US3697898A - Plural cavity bandpass waveguide filter - Google Patents

Plural cavity bandpass waveguide filter Download PDF

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Publication number
US3697898A
US3697898A US35869A US3697898DA US3697898A US 3697898 A US3697898 A US 3697898A US 35869 A US35869 A US 35869A US 3697898D A US3697898D A US 3697898DA US 3697898 A US3697898 A US 3697898A
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Prior art keywords
coupling
cavities
cavity
modes
waveguide
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US35869A
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Bruno L Blachier
Andre R Champeau
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International Telecommunications Satellite Organization
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Comsat Corp
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/16—Auxiliary devices for mode selection, e.g. mode suppression or mode promotion; for mode conversion
    • H01P1/161—Auxiliary devices for mode selection, e.g. mode suppression or mode promotion; for mode conversion sustaining two independent orthogonal modes, e.g. orthomode transducer
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
    • H01P1/2082—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure with multimode resonators
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P7/00—Resonators of the waveguide type
    • H01P7/06—Cavity resonators

Definitions

  • ABSTRACT A waveguide filter having two cascaded double-tuned cavities which are resonant in two independent orthogonal modes and provide a bandpass response. An elliptic function is obtained from the bandpass microwave filter structure by using a direct-coupling iris which selectively couples identical resonant modes between adjacent cavities.
  • the subject matter of the present invention is 5 generally concerned with the use of plural doubletuned resonant cavities to approximate the behavior of complex lumped element microwave filters. More particularly, the invention is a bandpass microwave filter including a plurality of coupled resonant cavities, each of which is tuned to support more than one independent mode of propagation at frequencies within a given pass band. A plurality of irises selectively couple propagating modes in each resonant cavity.
  • the medium is typically a hollow element of circular, rectangular or a square cross section which guides the propagating wave from one point to another with a minimum of distortion and attenuation.
  • the wave transmitted down such a waveguide will typically have a single polarization. However, depending upon the shape of a cross section of the waveguide, the wave may propagate with more than one polarization. Should the wave be confined to a particular length of waveguide it may oscillate at its natural resonant frequencies in more than one mode. A cavity, defined by this length of waveguide, will behave like a conventional resonant circuit and can provide a filtering function equivalent to the lumped element resonant circuit.
  • the single cavity filter may not provide sufficient off-band attenuation to give the desired frequency selectivity, a plural cavity design canbe used to provide this selectivity.
  • the plurality of cavities may be directly coupled together as a series of resonant elements by quarter wavelengths of transmission line tions Microwave Theory and Technique, Volume 17,
  • a cavity may resonate in more than one independent mode at its natural frequencies.
  • the modes resonating in a waveguide cavity may have an orthogonal orientation, that is, a vertical polarization and a horizontal polarization.
  • an orthogonal orientation that is, a vertical polarization and a horizontal polarization.
  • the present invention provides a lighter, more compact structure for achieving the bandpass response functions discussed above.
  • the invention uses N physical waveguide cavities which resonate in two independent orthogonal modes and are coupled together to provide the filtering capacity of 2N cavities resonating in a single mode.
  • the coupling is provided by structural discontinuities within the physical cavity.
  • the discontinuity may be a screw mounted in the cavity wall.
  • One feature of the invention is the use of selective polarization discriminating couplings between the N cavities to transfer energy between identical modes in the coupled cavities.
  • the selective couplings may be polarization discriminating irises, transmission lines or microwave bridge elements.
  • a further feature of the invention is the use of a phase inversion means in coupled cavities to provide a subtraction capability between identical modes in the coupled cavities. This subtraction capability can provide steep response skirts for the pass band of a filter.
  • FIG. 1a illustrates a filter configuration having two resonant cavities and embodying the principles of the present invention.
  • FIG. 1b is a drawing of the different electrical field polarizations along the length of the filter shown in FIG. la.
  • FIG. 2a is a drawing of a typical lumped element 1r network which at low frequencies provides the elliptical function response.
  • FIG. 3 is an illustration of the typical elliptic function response.
  • FIG. la illustrates a preferred embodiment of the invention which defines the fundamental principles that distinguish the invention from the prior art.
  • a circular waveguide section 1 which may be typically coupled to a rectangular waveguide at joints 2 and 3, is limited at both ends by reflective plates 4 and 5.
  • the circular section is divided by a third reflective plate 6 which defines two physical cavities 7 and 8. Since, in general, frequency is inversely proportional to wavelength (A) and the resonant frequency of a cavity is proportional to its length, selectivity at the desired center frequency requires that each of the filters physical cavities be typically )t/2 in length.
  • Each physical cavity is capable of resonating in two independent orthogonal modes at the center frequency of the usable bandwidth of the waveguide.
  • the principles applicable to this type of circular waveguide filter operating in the H mode may obviously be extended to waveguides having square, rectangular or elliptical cross sections which are capable of supporting two or more independent modes at a resonant frequency.
  • the circular waveguide filter is preferred due to its better selectivity, lower insertion losses and smaller weight.
  • the polarization of the resonant orthogonal modes is conventionally defined by horizontal and vertical vectors as shown in FIG. lb which are independent of each other and can propagate within the cavity without interference. If the cavity has perfect symmetry and proper dimensions, both modes will propagate at the same frequency. However, this structural condition is not obtainable in practice, and it is convenient to provide two tuning screws, symmetrically inserted into the cavity along radii which are coincident with the horizontal and vertical vectors of the orthogonal modes, to permit the independent tuning of both modes to the same desired frequency. Tuning screws 9 and 10 are placed in the walls of the first cylindrical cavity 7 to provide a capacitive tuning capacity for the cavity over a portion of the frequency band in the respective vertical and horizontal modes.
  • Tuning screws 11 and 12 are similarly mounted in the walls of cavity 8 to provide a capacitive tuning capacity. All fundamental modes propagating in the filter may thereby be tuned to the same desired frequency. These tuning screws are normally placed at the center of the cavity at a distance of approximately (M4), where electric fields are a maximum and the action of the screws is most effective, and where currents are at a minimum and negligible additional losses are introduced.
  • M4 approximately
  • Coupling screws 13 and 14 are also mounted into the wall of each of the respective cavities 7 and 8 at the center of the cavity where electric fields are at a maximum.
  • Each screw 13 and 14 provides a means, inside the cavity, which is capable of coupling the electric field from one of the independent orthogonal modes to the other.
  • the screws are oriented along a radius at a 45 angle to the fundamental orthogonal mode vectors to insure maximum coupling from one mode to the other and to provide an identical effect on the frequency of both modes.
  • Couplingscrew 14 is mounted in cavity 8 at an angle of 45 between the two orthogonal modes and is shifted by 90 from the radial orientation of screw 13.
  • the coupling provided by screw 14 is, therefore, equal to the coupling provided by screw 13 but of opposite sign. As will be shown below, this difference of sign in the two cavities is necessary to achieve the elliptic function response of the filter.
  • the degree of coupling is preferably adjusted by varying the length of the coupling screw which extends into the cavity.
  • the capacitive coupling effect may also be provided by any equivalent structural discontinuity within the cavity such as a dielectric rod or dent in the waveguide wall.
  • FIG. 1b illustrates a vector representation of the input wave V, and the output wave V which are assumed to have a vertical polarization in the rectangular waveguide of the preferred embodiment. Propagation within the cavities 7 and 8 is, however, in the cross polarized mode andreflection of the coupled, horizontal mode at plates 4 and 5 without transmission to the rectangular waveguide is necessary to support resonance in the dual mode.
  • the geometry and orientation of the coupling slots 15 and 16 are selected to maximize coupling of any incoming and outgoing waves having the proper polarization, but to minimize coupling of other polarizations and to confine the opposite component of the resonating cross polarized waves within cavities 7 and 8.
  • the irises are rectangular slots which are narrow with respect to their length to achieve good polarization discrimination.
  • slots are oriented in the waveguide to pass the vertically polarized input and output waves but to reflect the horizontal component of the resonant cross polarized mode within the cavities. Accordingly, the slot lengths are positioned to be normal to the vertically polarized mode and parallel to the horizontally polarized mode.
  • the input structure need not be limited to a rectangular waveguide which transmits waves having a single polarization. Any other kind of transmission line may be used which propagates signals having one or more modes, provided that adequate polarization discriminating coupling at the input is achieved.
  • other geometries and orientations of the coupling structure at the input and output to the filter may be selected to pass waves having a desired polarization into and out of the resonant cavities and to reflect the undesired components of the orthogonally polarized waves within the cavities.
  • This iris has, typically, a geometrical configuration and an orientation which will selectively couple each of the orthogonal modes resonating in the cavities 7 and 8.
  • the horizontal mode propagating in resonant cavity 7 be maximally coupled to the horizontal mode propagating in resonant cavity 8 and that some lesser degree of coupling exist between the vertically polarized modes of cavities 7 and 8.
  • FIG. la A unique geometrical configuration is shown in FIG. la for the iris 17.
  • the coupling slot can be viewed as two overlapping, horizontal and vertical slots which are symmetrically oriented to coincide with the orthogonal vectors defining the two propagating modes in the respective physical cavities.
  • the dimensions of the slot 17 are selected to provide the desired degree of coupling of the horizontal and the vertical modes.
  • other coupling means such as quarter wave length lines or additional geometrical configurations for the iris 17 may be used to provide the desired degree of coupling between the horizontal and vertical modes in each of the cavities.
  • perfect polarization discrimination is not necessary and rectangular or elliptical shapes giving different degrees of coupling between the two modes may be selected.
  • the iris structure illustrated in FIG. 1a has been proven to provide the desired independent control over the degree of coupling of the two orthogonal modes.
  • iris 17 The vertical dimensions of iris 17 are selected to inductively couple the horizontal mode R2 of the electric field existing in cavity 7 to the cavity 8 as horizontal resonant mode R3.
  • Mode R3 will be coupled to the vertical resonant mode R4 by coupling screw 14, resulting in the simultaneous and independent propagation of the crossed modes R3 and R4 within cavity 8.
  • coupling screw 14 is oriented at a angle to coupling screw 13 and therefore imparts a 180 phase shift to vertical resonant mode R4 with respect to vertical mode R1.
  • each of the cavities 7 and 8 have horizontal modes which are identical in phase and magnitude, however, the vertical modes are seen to be 180 out of phase.
  • the horizontal dimension of iris 17 provides a coupling between the vertical mode R1 in cavity 7 and the vertical mode R4 in cavity 8.
  • the coupling of these two modes which are 180 out of phase will provide the desired elliptic function.
  • the coupling of modes R4 and R1 is smaller than the coupling of modes R2 and R3 and will only cancel the frequency response of the filter at the edges of the pass band resulting in the characteristic steep sides and notches of the elliptic filter response as seen in FIG. 3.
  • FIG. la may be represented by an equivalent lumped element circuit and techniques for converting the functions of a microwave element to a circuit element have been examined in Microwave Transmission Circuits, Volume 9, MIT Radiation Laboratory Series, pp. 661-706.
  • FIG. 2a is a circuit diagram of the classic 1r section which at low frequencies provides the elliptical function response shown in FIG. 3.
  • FIG. 2b is a lumped element filter, derived from the 'rr section of FIG. 2a, which by conventional circuit synthesis techniques is equivalent to the light weight microwave structure of the present invention and provides an identical elliptical function response.
  • the equivalent circuit illustrated in FIG. 2b, consists of four parallel tank circuits connected by two inductive couplings and two capacitive couplings.
  • the first section of the physical cavity 7 resonates in mode R1 and R2 and is equivalent to the first resonant parallel circuits and 111 respectively in FIG. 2b.
  • resonant circuits 112 and 113 are equivalent to the resonant modes R3 and R4 present in the second physical cavity.
  • the capacitive tuning screws 9 and 10 are equivalent to the capacitors 1 14 and l 15.
  • the coupling between vertical mode R1 of the first physical cavity and horizontal mode R2 of the first physical cavity is equivalent to the capacitive coupling element 1 16.
  • Tuning screws 11 and 12 are equivalent to the capacitors 117 and 118, while capacitive coupling screw 14 is equivalent to the capacitive coupler 1 19.
  • the input and output irises l5 and 16 are inductive devices which are assumed to provide a lossless coupling of the waveguide to the filter; consequently, the two irises are equivalent to perfect transformers 120 and 121 which transfer all power in the input signal to the cavities and from the cavities to the output circuit.
  • the tank circuit 113 whose resonance is equivalent to resonant mode R4
  • the input from coupling capacitance 119 is inverted in phase by a crossover circuit 122 which is equivalent to the displacement of the coupling screw by 90.
  • the output of this tank circuit is fed back to the input tank circuit by an inductor 123 which is equivalent to the inductive coupling of mode R4 to mode R1 through the horizontal portion of iris 17.
  • the feedback of this negative resonant signal to the first resonant circuit provides the steep slope and the notches in the elliptical function response.
  • the interconnection of identical modes in the N cavity case may obviously be accomplished through the irises of cascaded cavities or may conveniently be facilitated by the direct connection of the cavities by polarization discriminating waveguide bridge elements.
  • the cavities may be in-line or may be folded to achieve a compact filter structure.
  • a plural cavity waveguide filter comprising,
  • first discontinuity coupling means oriented in each of said cavities for intra coupling said first mode to said second mode
  • second coupling means connecting selected ones of said cavities for inter coupling like oriented modes in said selected cavities said second coupling means including polarization discriminating means adapted to provide selective inter coupling between like oriented modes in said cavities.
  • first coupling means is adaptable to provide either an intra coupling having a first phase or an intra coupling having a second phase differing from said first phase by 180.
  • said second coupling means includes a reflective plate directly connecting two of said cavities, said plate including an iris for selectively inter coupling the identical modes in said two cavities.
  • said filter includes tuning means in each of said cavities for independently tuning each of said modes to the cavity resonant frequency.
  • said second coupling means is a reflective plate having a coupling iris, the dimensions of said iris being selected to provide said selective inter coupling between identical modes.
  • said waveguide cavities are cylindrical waveguide sections and wherein said tuning means includes two adjustable screws mounted in said waveguide sections and coincidently disposed along said independent orthogonal resonant modes.
  • said plurality of cavities include an input and an output cavity, said input cavity being coupled to an input waveguide by a first reflective plate having a polarization discriminating coupling iris, and said output cavity of the filter is connected to'an output waveguide by a second reflective plate having a polarization discriminating iris.
  • a waveguide filter having an elliptic function response comprising:
  • tuning means in each of said cavities for independently tuning each of said resonant modes to its resonant frequency
  • coupling means in said first cavity for capacitively intra coupling said first resonant mode to said second resonant mode
  • coupling means in said second cavity for capacitively coupling said first resonant mode to said second resonant mode and for shifting the phase of said second mode by with respect to said first mode of said first cavity;
  • inductive coupling means for selectively inter coupling said first resonant modes and said second resonant modes in said cavities.
  • tuning means comprise two screws, mounted in the wall of each cavity, which are coincident with the vectors of said orthogonal modes.
  • said inductive coupling means is a first reflective plate having a coupling iris whereby the degree of coupling between identical modes in each cavity is selectively adjusted by varying the dimensions of said iris.
  • An elliptic filter as recited in claim 12 wherein said first cavity of the filter is connected to an input waveguide by a second reflective plate having a polarization discriminating coupling iris, and said second cavity of the filter is connected to an output waveguide by a third reflective plate having a polarization discriminating coupling iris.
  • a filter as recited in claim 9 wherein a plurality of said first and second waveguide cavities are connected in cascade and wherein said inductive coupling means includes a first means for directly connecting adjacent cavities and a second means for inter connecting selected cavities.

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US35869A 1970-05-08 1970-05-08 Plural cavity bandpass waveguide filter Expired - Lifetime US3697898A (en)

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JP (1) JPS5116094B1 (enrdf_load_stackoverflow)
BE (1) BE766286A (enrdf_load_stackoverflow)
DE (1) DE2122337C2 (enrdf_load_stackoverflow)
FR (1) FR2100640B1 (enrdf_load_stackoverflow)
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US3936775A (en) * 1974-09-30 1976-02-03 Harvard Industries, Inc. Multicavity dual mode filter
US3969814A (en) * 1975-01-15 1976-07-20 Trw Inc. Method of fabricating waveguide structures
US4030051A (en) * 1976-07-06 1977-06-14 Hughes Aircraft Company N-section microwave resonator having rotary joint for variable coupling
US4060779A (en) * 1976-12-27 1977-11-29 Communications Satellite Corporation Canonical dual mode filter
US4135133A (en) * 1977-03-14 1979-01-16 Rca Corporation Dual mode filter
US4180787A (en) * 1976-11-30 1979-12-25 Siemens Aktiengesellschaft Filter for very short electromagnetic waves
US4218666A (en) * 1979-04-27 1980-08-19 Premier Microwave Corporation Dual mode band rejection filter
US4260967A (en) * 1979-03-26 1981-04-07 Communications Satellite Corporation High power waveguide filter
US4410865A (en) * 1982-02-24 1983-10-18 Hughes Aircraft Company Spherical cavity microwave filter
US4489293A (en) * 1981-05-11 1984-12-18 Ford Aerospace & Communications Corporation Miniature dual-mode, dielectric-loaded cavity filter
US4498061A (en) * 1981-03-07 1985-02-05 Licentia Patent-Verwaltungs-Gmbh Microwave receiving device
FR2555368A1 (fr) * 1983-11-18 1985-05-24 Europ Agence Spatiale Filtre micro-onde integre et procede de construction d'un tel filtre
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US5867077A (en) * 1996-10-15 1999-02-02 Com Dev Ltd. Temperature compensated microwave filter
US5909159A (en) * 1996-09-19 1999-06-01 Illinois Superconductor Corp. Aperture for coupling in an electromagnetic filter
EP0899808A3 (en) * 1997-08-26 2000-01-12 Hughes Electronics Corporation Dual mode cavity resonator with coupling grooves
US6046658A (en) * 1998-09-15 2000-04-04 Hughes Electronics Corporation Microwave filter having cascaded subfilters with preset electrical responses
EP1020946A1 (de) * 1999-01-15 2000-07-19 Robert Bosch Gmbh Hohlraumresonator mit Mitteln zur Abstimmung seiner Resonanzfrequenz
US6100703A (en) * 1998-07-08 2000-08-08 Yissum Research Development Company Of The University Of Jerusalum Polarization-sensitive near-field microwave microscope
US6297715B1 (en) 1999-03-27 2001-10-02 Space Systems/Loral, Inc. General response dual-mode, dielectric resonator loaded cavity filter
US6898419B1 (en) * 2001-04-30 2005-05-24 Nortel Networks Corporation Remotely adjustable bandpass filter
US20100079354A1 (en) * 2008-03-12 2010-04-01 The Boeing Company Lens for Scanning Angle Enhancement of Phased Array Antennas
US20100328175A1 (en) * 2009-06-25 2010-12-30 Lam Tai A Leaky cavity resonator for waveguide band-pass filter applications
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US8487832B2 (en) 2008-03-12 2013-07-16 The Boeing Company Steering radio frequency beams using negative index metamaterial lenses
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Cited By (53)

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Publication number Priority date Publication date Assignee Title
JPS50138757A (enrdf_load_stackoverflow) * 1974-04-08 1975-11-05
US3936775A (en) * 1974-09-30 1976-02-03 Harvard Industries, Inc. Multicavity dual mode filter
US3969814A (en) * 1975-01-15 1976-07-20 Trw Inc. Method of fabricating waveguide structures
US4030051A (en) * 1976-07-06 1977-06-14 Hughes Aircraft Company N-section microwave resonator having rotary joint for variable coupling
US4180787A (en) * 1976-11-30 1979-12-25 Siemens Aktiengesellschaft Filter for very short electromagnetic waves
US4060779A (en) * 1976-12-27 1977-11-29 Communications Satellite Corporation Canonical dual mode filter
DE2754927A1 (de) * 1976-12-27 1978-06-29 Communications Satellite Corp Hohlleiterfilter mit mehreren hohlraeumen
US4135133A (en) * 1977-03-14 1979-01-16 Rca Corporation Dual mode filter
US4260967A (en) * 1979-03-26 1981-04-07 Communications Satellite Corporation High power waveguide filter
US4218666A (en) * 1979-04-27 1980-08-19 Premier Microwave Corporation Dual mode band rejection filter
US4498061A (en) * 1981-03-07 1985-02-05 Licentia Patent-Verwaltungs-Gmbh Microwave receiving device
US4489293A (en) * 1981-05-11 1984-12-18 Ford Aerospace & Communications Corporation Miniature dual-mode, dielectric-loaded cavity filter
US4410865A (en) * 1982-02-24 1983-10-18 Hughes Aircraft Company Spherical cavity microwave filter
US4544901A (en) * 1982-06-11 1985-10-01 Agence Spatiale Europeenne Microwave filter structure
EP0104735A3 (en) * 1982-09-27 1986-03-12 Ford Aerospace & Communications Corporation Electromagnetic filter with multiple resonant cavities
US4571563A (en) * 1983-11-18 1986-02-18 Agence Spatiale Europeenne Integrated microwave filter and method of constructing same
FR2555368A1 (fr) * 1983-11-18 1985-05-24 Europ Agence Spatiale Filtre micro-onde integre et procede de construction d'un tel filtre
US4549310A (en) * 1984-03-29 1985-10-22 Rca Corporation Cross-polarization corrector for circular waveguide
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Also Published As

Publication number Publication date
FR2100640A1 (enrdf_load_stackoverflow) 1972-03-24
NL7106401A (enrdf_load_stackoverflow) 1971-11-10
DE2122337A1 (de) 1971-11-25
FR2100640B1 (enrdf_load_stackoverflow) 1978-03-24
NL174509C (nl) 1984-06-18
JPS5116094B1 (enrdf_load_stackoverflow) 1976-05-21
DE2122337C2 (de) 1983-01-13
NL174509B (nl) 1984-01-16
BE766286A (fr) 1971-09-16
SE364143B (enrdf_load_stackoverflow) 1974-02-11
GB1301972A (enrdf_load_stackoverflow) 1973-01-04

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