US3142763A - Circuit arrangement for supplying an impedance with current pulses - Google Patents

Circuit arrangement for supplying an impedance with current pulses Download PDF

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Publication number
US3142763A
US3142763A US842441A US84244159A US3142763A US 3142763 A US3142763 A US 3142763A US 842441 A US842441 A US 842441A US 84244159 A US84244159 A US 84244159A US 3142763 A US3142763 A US 3142763A
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Prior art keywords
impedance
voltage
emitter
transistor
current
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US842441A
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English (en)
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Traas Laurus Jan
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US Philips Corp
North American Philips Co Inc
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US Philips Corp
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H03K17/64—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors having inductive loads

Definitions

  • cmcurr mmcsum FOR suy umc an, xursnmcs: um cuaasn'r PULSES Filed Sept. 25. 1959 INVENTOR Icarus an trues BY M W AGE United States Patent Ofiice 42,763 CIRCUIT ARRANGEMENT FOR SUPPLYING, AN
  • the present invention relates to circuit arrangements for feeding an impedance with current pulses having a substantially constant amplitude substantially independent of the voltage drop across the impedance; the impedance is usually fed through a regulating impedance and the main current electrode path of a transistor acting as 1 i a switch, the former of which mainly determine the pulse amplitude.
  • FIG. 1 of the accompanying drawing the most obvious solution is that of FIG. 1 of the accompanying drawing;
  • the current pulses are generated by closing'aswitch 1, as a result of which the voltage E of a-supply is applied via a regulating impedance 2, across the impedance 3 to be supplied. If the regulating impedance 2 is high in proportion tothe impedance 3,
  • a typical example of the use of a transistor as a switch for feeding an impedance with current pulses is that in which the impedance is formed by many series-connected control windings of memory cores, such as are found in the matrix memory. system of a computer.
  • the impedance is represented as such a series-combination of windings which usually consist of a wire threaded through the cores 4 to be controlled.
  • the amplitude I of the current pulses must not vary by more than approximately that the regulating impedance 2 is a resistor having a value R compared to which the resistance of the series of windings on the cores 4 is negligible, and that, if all the cores have been read in and their magnetization is reversed or they are demagnetized by the current pulse, a' maximum reverse voltage V, is generated across the impedance 3, then we have i max- 2 nomlnal- 2 if the magnetization of none of the cores is reversed by the current pulse, and:
  • sipated in the resistor R is unduly high. If the switch 1 I is a transistor, R should be at least so high that the transistor is bottomed when in the conductive state, so that reduction of the dissipated power (1').R, cannot be reached by reduction of R Besides, when assuming the same tolerances for the current I through the windings of a number of cores to be controlled, the new condition:
  • E must necessarily be of the same order as V and as E, for example equal to E.
  • a voltage higher than that permissible for the switch transistor is applied, via the output circuit of the current amplifiento the series-combination of the regulating impedance, the main current electrode path of the switching transistor, and the impedance to be supplied, while the voltage across the switching transistor is limited by a so-called clamping diode which is connected in the forward direction with respect to the current through th main current electrode path of the switching transistor. This is in the direction opposite to that of the diode 5 of FIG. 2.
  • the condition (3) is not changed by this additional measure, yet the supply voltage E for the switching transistor and the value R of the regulating imso that the maximum voltage drop V across the impedance to be fed which can still be compensated is, for example, only 1 v.'smaller than the maximum permissible voltage V, or V of the switching transistor. If the current amplifier is equipped with a second transistor, the higher voltage E should be lower than the maximum permissible voltage for this transistor, while a second separating diode prevents a voltage drop of reverse direction across the' impedance to be supplied from being superimposed on the supply voltage E of this transistor.
  • FIG. 3 is the basic circuit diagram
  • FIGS. 4 to 6 are circuit diagrams of three dilierent embodiments of the circuit arrangement according to the invention.
  • the basic circuit diagram represented in FIG. 3, comprises a switch 1, one contact of which is connected to the negative terminal of a source of supply voltage E and to ground via a load impedance 3.
  • the other contact of the switch is connected to the positive terminal of the supply source via a regulating impedance 2 and 0. consists or the series-combination of control windings of a comparatively large number of memory cores 4.
  • This voltage value of the impedance 3 and this value is in turn dependent on the condition of the memory cores 4. If all the cores have been read in beforehand, their magnetization is again reversed by the current pulse and consequently a comparatively high voltage pulse is produced across the impedance 3.
  • This voltage pulse counteracts the current pulse supplied to this impedance via the switch 1, so that, under these conditions, the amplitude of the control pulseis comparatively strongly reduced. If, however, none of the cores 4 has been read in, not a single core will flip from one condition of magnetic saturation into the reverse condition of magnetic saturation by the current pulse. Consequently,
  • the amplitude of this current pulse is larger than in the preceding case, because the reverse voltage produced across the impedance 3 is lower.
  • the described change in amplitude of the control current pulses due to the presence of the impedance 3 is objectionable for the satisfactory operation of a device having magnetic memory cores, for example of a matrix of a computer or of an automatic system such as an automatic selection equipment.
  • a control current pulse may happen to be too small to make all the cores 4 re- I assume the same state of magnetic saturation. It is consequently desirable to maintain and/ or regulate the amplitude of the control current pulses within given limits. So long as the number of memory cores 4 is not too large, this can be effected by means of the regulating imped ance 2 and by corresponding increase of the voltage of the supply source E.
  • the voltage drop across this impedance 3 is amplified by means of a current amplifier 6 and converted into corresponding current pulses, which are taken from the output circuit of this amplifier and fed back to the impedance 3 via the switch 1.
  • the voltage drop across the impedance 3 is supplied to the input terminals 7 of the current amplifier 6 and the output circuit of this current amplifier constitutes the regulating circuit 8 and is connected in series with the source of supply voltage E across the series-combination of the regulating impedance 2, of the switch 1 and of the impedance 3 to be supplied.
  • the voltage is supplied to the input terminals 7 of the current amplifier 6 and the output circuit of this current amplifier constitutes the regulating circuit 8 and is connected in series with the source of supply voltage E across the series-combination of the regulating impedance 2, of the switch 1 and of the impedance 3 to be supplied. The voltage.
  • the amplitude of the control current pulses through the impedance 3 is only dependent on the voltage of the supply source B and on the value of the regulating impedance 2, which voltage and which value can be chosen at will so as to supply the impedance 3 with current pulses of the desired amplitude.
  • the switch 1 is formed by a junction transistor of the npn-type in common emitter arrangement, the base of which is controlled by positive control pulses supplied via a transformer 9 the secondary winding 10 of which is connected between the ed via a comparatively high-value resistor 15.
  • the diode 13 is connected inthe forward direction with respect, to voltage pulses produced across the impedance 3 by current pulses via the transistor 1. These voltage pulses are thus transmitted, via this diode and via the capacitor 14, to the base of the transistor 11 which produces a corresponding increase in voltage across the series combination connected in its emitter circuit and 'comprising the resistor 22, the collector-emitter circuit of the transistor 1 and the impedance 3.
  • the amplitude of the current pulses through the impedance 3 is consequently approximately equal to the quotient of the voltage E and of the value R of the resistor 22.
  • the sole object of the resistor 21 is to pass a current through the impedance 3, the transistor 1 and the resistor 22 at the beginning of each control current pulse.
  • the time constant of the capacitor 14 in connection with resistor 12 and with the forward input resistance of the transistor 11 connected in parallel therewith should be large with respect to the duration of the control current pulses to be supplied to the impedance 3.
  • the current amplifier comprises a second transistor 16, the base of which is directly connected to the common point of the diode 13 and of the resistor 15.
  • The'emitter of this transistor 16 is grounded via a load resistor 17 and its collector is directly connected to the positive terminal +E of a source of higher supply voltage.
  • the emitter circuit of the transistor 16 consequently forms a source of pulse voltage of comparatively small internal resistance, and the voltage pulses produced at its emitter and corresponding to the positive voltage pulse across the impedance 3 to be supplied are transmitted to the supply circuit for the collector of the transistor 1 via a high-value capacitor 14'.
  • This supply circuit comprises the series-cor'nbination of the supply source E, of a diode 18 connected in the forward direction with respect to a current from this source, and of the regulating impedance formed by a resistor 22.
  • the current amplifier with the transistor 16 and via the capacitor 14' the voltage at the common point of the diode 18 and of the resistor 22 is increased by the amount of the voltage drop across the lgg'rad resistor 17, which voltage drop is approximately equal to the voltage drop produced across the impedance 3 by control current pulse via the transistor 1.
  • the time constant of the capacitor 14' in connection with the resistor 22 should be large with respect to the duration of the control. current pulses to be supplied to the impedance 3. Sometimes, this condition is difficult to meet without using a comparatively costly capacitor of unduly large size.
  • the voltage at the collector of the transistor 1 cannot exceed that of the supply source E, since the diode 18 is then conductive:
  • the voltage at the collector of the transistor 1 then cut 011 is thus practically equal to the voltage at the terminal +E.
  • this diode 18 is blocked by the current pulses taken from the emitter circuit of the transistor 16 via the capacitor 14', when the transistor 1 is conductive and the voltage between its emitter and collector electrodes is very low, for example a few tenths of a volt.
  • the voltage drop across the impedance 3 to be supplied is thus compensated by a voltage which is not taken from the supply source E and which is added to the voltage of this source.
  • the current amplifier comprises three stages.
  • the first stage comprises a transistor 16 connected similarly to the transistor 16 of the example shown in FIG. 5 with the dilference that its emitter is not connected to the main circuit for sup-
  • This transistor is again connected as an emitter-follower and, like the transistor 16, is fed from the supply source of higher voltage E.
  • Its emitter circuit comprises a load resistor 27 and its emitter is coupled to the base of the transistor 11 of the third stage via a capacitor 14.
  • the transistor of the third stage corresponds to, the transistor 11 shown in FIG. 4 and is connected in the same manner, with the difference that the resistor 21 of FIG. 4-has been replaced by the diode 18 shown in FIG. 5 in series-combination with decoupled resistors 28 and 29.
  • a capacitor 32 is connected in parallel with the resistor 28.
  • This capacitor is to supply a current through the regulating resistor 22, the diode 18, the collectoremitter electrode path of the transistor 1 and the impedance 3 to be supplied, during the very short time between the instant at which the transistor 1 becomes con ductive as a result of a control pulse applied between its baseand emitter-electrodes and the instant at which the transistor 11 also becomes conductive as a result of the voltage drop across the impedance 3, transmitted toits base electrode via the diode 13, the emitter-followers with the transistors 16 and 26, and the connecting capacitor 14. Consequently, this capacitor 32 does 'not need to have a high value and the circuit arrangement has the advantage of being supplied from a single supply source having the voltage E.
  • the collectors of the transistors 16 and 26 are connected to the common point of the resistors 28 and 29, so that the transistor 11 can never be bottomed, since its base potential remains smaller than its collector potential by voltage drop across the resistor 28. Also this second tapping of the voltage divider 28, 29, 30 is decoupled by means of a capacitor 31.
  • the impedance to be supplied is shunted by a diode 13 connected in the forward direction with respect to the voltage drop produced across this impedance by a current pulse via the transistor 1 and connected in series with a resistor 15 and with the baseemitter circuit of a transistor, 11 and 16 respectively,
  • control current pedance 3 by a corresponding amount, so that it is de- I sirable to keep it as low as possible. If the amplifier 6 comprises more than one stage, this control current can be strongly reduced. A further reduction of this control current can be obtained by replacing the transistor 16 of the first stage of the amplifier.6 by a tube in cathode-follower arrangement, for example by a small triode for low anode voltage. can be connected directly to the emitter of the transistor 1, omitting the diode 13 and the resistor 15.
  • a circuit arrangement for feeding current pulses having substantially constant amplitude to a load impedance comprising a switching transistor having base, emitter and collector electrodes and an emitter-collector elec- The grid of this triode trode path, a regulating impedance and a load impedance connected in series with said emitter-collector path, a
  • source of supply voltage poled to bias said emitter elecput circuits said input circuit being coupled to said load impedance, said output circuit being coupled to said regulating'impedance, compensating current pulses being produced in said output circuit in response to the voltage drop produced across said load impedance when a current-pulse is fed to said load impedance via said regulating impedance and said emitter-collector electrode path, said compensating current pulses being superimposed on said current pulses and compensating for the influence of said voltage drop upon the amplitude of the current pulses.
  • said current amplifier comprising an additional transistor having base, emitter and collector electrodes, said amplifier being connected in grounded collector arrangement, said input circuit including the base electrode of the amplifier.
  • a circuit arrangement as claimed in claim 1, said current amplifier comprising an additional transistor havingbase, emitter and collector electrodes, said amplifier being connected in grounded collector arrangement, said input circuit including the base electrode of the amplifier, a diode connected between said .load impedance and the base electrode of said amplifier, said diode having a polarity such that the voltage drop produced across the load impedance is applied to the amplifier base electrode.
  • said current amplifier comprising an additional transistor having base, emitter and collector electrodes, said amplifierv being connected in grounded collector arrangement, said input circuit including the base electrode of the amplifier, a diode connected between said load impedance and the base electrode of said amplifier, said diode having a polarity such that the voltage drop produced across the load impedance is applied to the amplifier base electrode.
  • a circuit arrangement for feeding current pulses having substantially constant amplitude to a plurality of series-connected control windings of magnetic memory cores, each of said cores having a substantially rectangular hysteresis loop and being capable of independently assuming a distinct remanence condition comprising: a switching transistor having base, emitter and collector electrodes and an emitter-collector electrode path, a regulating impedance, said core control windings being connected in series with said regulating impedance and said emitter-collector path, a source of supply voltage poled tobias said emitter electrode in the forward direction, means for applying control current pulses in the conducting direction to said base electrode, a current amplifier having inputand output circuits, said input circuit being coupled to said series-connected control windings, said output circuit being coupled to said regulating impedance, compensating current pulses being produced in said output circuit in response to the voltage drop produced across said control windings when a current pulse is fed to said windings via said regulating impedance and said emitter-collector electrode path

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Amplifiers (AREA)
  • Dc-Dc Converters (AREA)
  • Networks Using Active Elements (AREA)
  • Electronic Switches (AREA)
US842441A 1958-10-03 1959-09-25 Circuit arrangement for supplying an impedance with current pulses Expired - Lifetime US3142763A (en)

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NL231959 1958-10-03

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US (1) US3142763A (de)
CH (1) CH393422A (de)
DE (1) DE1091610B (de)
FR (1) FR1236934A (de)
GB (1) GB929786A (de)
NL (1) NL103758C (de)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3624418A (en) * 1969-12-17 1971-11-30 Control Data Corp Push-pull floating driver

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2811941B2 (ja) * 1990-09-05 1998-10-15 富士電機株式会社 スイッチングトランジスタの制御回路

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2751549A (en) * 1954-01-04 1956-06-19 Bell Telephone Labor Inc Current supply apparatus
US2832900A (en) * 1957-02-12 1958-04-29 Gerald M Ford Transient overvoltage and short circuit protective network
US2878440A (en) * 1957-03-28 1959-03-17 Navigation Computer Corp Regulated power supply
US2888633A (en) * 1958-05-09 1959-05-26 Collins Radio Co Voltage regulator with limited current drain
US2912635A (en) * 1956-11-01 1959-11-10 Ford Motor Co Electrical regulator device for generators
US2916705A (en) * 1955-05-31 1959-12-08 Philips Corp Electric circuit arrangement for generating substantially linear voltage changes

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2751549A (en) * 1954-01-04 1956-06-19 Bell Telephone Labor Inc Current supply apparatus
US2916705A (en) * 1955-05-31 1959-12-08 Philips Corp Electric circuit arrangement for generating substantially linear voltage changes
US2912635A (en) * 1956-11-01 1959-11-10 Ford Motor Co Electrical regulator device for generators
US2832900A (en) * 1957-02-12 1958-04-29 Gerald M Ford Transient overvoltage and short circuit protective network
US2878440A (en) * 1957-03-28 1959-03-17 Navigation Computer Corp Regulated power supply
US2888633A (en) * 1958-05-09 1959-05-26 Collins Radio Co Voltage regulator with limited current drain

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3624418A (en) * 1969-12-17 1971-11-30 Control Data Corp Push-pull floating driver

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FR1236934A (fr) 1960-07-22
NL103758C (de)
CH393422A (de) 1965-06-15
DE1091610B (de) 1960-10-27
GB929786A (en) 1963-06-26

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