US10389233B1 - Switched mode power supply with PFC burst mode control - Google Patents

Switched mode power supply with PFC burst mode control Download PDF

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US10389233B1
US10389233B1 US16/154,156 US201816154156A US10389233B1 US 10389233 B1 US10389233 B1 US 10389233B1 US 201816154156 A US201816154156 A US 201816154156A US 10389233 B1 US10389233 B1 US 10389233B1
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mode
controller
voltage
output
input voltage
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Shu Fan Lim
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Infineon Technologies Austria AG
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Priority to TW108131551A priority patent/TWI824000B/zh
Priority to KR1020190123869A priority patent/KR20200040673A/ko
Priority to CN201910949140.6A priority patent/CN111010026A/zh
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4241—Arrangements for improving power factor of AC input using a resonant converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/425—Arrangements for improving power factor of AC input using a single converter stage both for correction of AC input power factor and generation of a high frequency AC output voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4266—Arrangements for improving power factor of AC input using passive elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0032—Control circuits allowing low power mode operation, e.g. in standby mode
    • H02M1/0035—Control circuits allowing low power mode operation, e.g. in standby mode using burst mode control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • CCM-DCM continuous conduction mode-discontinuous conduction mode
  • PFC power factor correction
  • average current control a reference inductor current is obtained by multiplying the output of the voltage mode controller with a rectified sinusoidal waveform obtained from the AC input voltage. The AC input voltage is needed to yield accurate current reference information for current regulation.
  • Burst/standby mode control for average current mode CCM PFC is typically implemented with AC input voltage measurements, which requires the controller to have a at least one pin for measuring the AC input voltage during burst mode.
  • the reference inductor current can be derived from the output of the voltage mode controller and the AC input voltage.
  • Current mode control ensures that the average inductor current tracks the reference inductor current during the burst-on period.
  • AC input voltage measurement may not be possible in burst mode.
  • Pin count is a factor in controller cost.
  • Some digital controllers minimize the number of pins to reduce cost.
  • the controller may have a single pin for both the AC input voltage measurement feature and an AC detection feature.
  • AC detection is used to detect if the AC input is disconnected, and to provide a low impedance path to quickly discharge an external capacitor when the AC input is disconnected.
  • AC input voltage measurements are typically done via a high impedance path to reduce power loss.
  • the AC detection feature is typically preferred over the AC input voltage measurement feature because of IEC safety requirement 62368-1.
  • the voltage across the external capacitor must be lower than 60V after 2 seconds from AC disconnect. Hence, AC input voltage measurements may not be available for many types of power supply controllers during burst mode.
  • the digital controller comprises: a current mode controller configured to operate the PFC stage in continuous-conduction mode (CCM) in a steady-state mode of the power supply, by implementing a current control loop which has AC input voltage measurements as an input; a voltage mode controller configured to operate the PFC stage in discontinuous-conduction mode (DCM) for at least part of a burst mode of the power supply, by implementing a voltage control loop which does not have AC input voltage measurements as an input; and an adaptive loop configured to modify the voltage control loop if an output of the voltage mode controller in the burst mode and which is proportional to power in average current mode control falls outside a predetermined range.
  • CCM continuous-conduction mode
  • DCM discontinuous-conduction mode
  • the predetermined range may define a maximum limit and a minimum limit on power delivered by the power supply in the burst mode, the maximum limit may correspond to a maximum value of the output of the voltage mode controller, and the minimum limit may correspond to a minimum value of the output of the voltage mode controller.
  • the maximum limit may be approximately 2 times a maximum load in the burst load. Separately or in combination, the maximum limit may be lower in the burst mode than in the steady-state mode.
  • the digital controller may be configured to determine an on-time for the PFC stage in the burst mode based on the output of the voltage mode controller, a DC equivalent value of an AC input voltage measurement taken prior to entering the burst mode, and an estimate of a conduction mode inductor current of the PFC stage, and the adaptive loop may be configured to modify the DC equivalent value of the AC input voltage measurement if the output of the voltage mode controller falls outside the predetermined range.
  • the estimate of the conduction mode inductor current of the PFC stage may be a constant value greater than 0 and less than 1.
  • the adaptive loop may be configured to decrease the DC equivalent value of the AC input voltage measurement if the output of the voltage mode controller is clamped at the maximum value or exceeds a target value, and the adaptive loop may be configured to increase the DC equivalent value of the AC input voltage measurement if the output of the voltage mode controller is clamped at the minimum value or is below the target value.
  • the adaptive loop may be configured to decrease or increase the DC equivalent value of the AC input voltage measurement in predetermined steps.
  • the adaptive loop may be an integrator or proportional-integral control loop configured to adjust the DC equivalent value of the AC input voltage measurement so that the output of the voltage mode controller moves towards a target value.
  • the integrator or proportional-integral control loop may be configured to compute a delta value based on the difference between the target value and the output of the voltage mode controller and add the delta value to the DC equivalent value of the AC input voltage measurement.
  • the adaptive loop may be configured to modify a step size of a change made to the DC equivalent value of the AC input voltage measurement if the change exceeds a predetermined threshold.
  • the adaptive loop may be enabled and performed every sampling period during a burst-on period of the PFC stage in the burst mode if the output of the voltage mode controller falls outside the predetermined range, and the adaptive loop may be disabled once the output of the voltage mode controller falls within the predetermined range.
  • the current mode controller may be configured to operate the PFC stage in CCM using the output of the voltage mode controller and the DC equivalent value of the AC input voltage measurement from the burst mode as initial values.
  • the power supply comprises: a power factor correction (PFC) stage; an LLC converter coupled to the PFC stage; a current mode controller configured to operate the PFC stage in continuous-conduction mode (CCM) in a steady-state mode of the power supply, by implementing a current control loop which has AC input voltage measurements as an input; a voltage mode controller configured to operate the PFC stage in discontinuous-conduction mode (DCM) for at least part of a burst mode of the power supply, by implementing a voltage control loop which does not have AC input voltage measurements as an input; and an adaptive loop configured to modify the voltage control loop if an output of the voltage mode controller in the burst mode and which is proportional to power in average current mode control falls outside a predetermined range.
  • PFC power factor correction
  • CCM continuous-conduction mode
  • DCM discontinuous-conduction mode
  • the method comprises: operating the PFC stage in continuous-conduction mode (CCM) in a steady-state mode of the power supply using a current mode controller, by implementing a current control loop which has AC input voltage measurements as an input; operating the PFC stage in discontinuous-conduction mode (DCM) for at least part of a burst mode of the power supply using a voltage mode controller, by implementing a voltage control loop which does not have AC input voltage measurements as an input; and modifying the voltage control loop if an output of the voltage mode controller in the burst mode and which is proportional to power in average current mode control falls outside a predetermined range.
  • CCM continuous-conduction mode
  • DCM discontinuous-conduction mode
  • the predetermined range may define a maximum limit and a minimum limit on power delivered by the power supply in the burst mode, the maximum limit may correspond to a maximum value of the output of the voltage mode controller, and wherein the minimum limit may correspond to a minimum value of the output of the voltage mode controller.
  • operating the PFC stage in DCM for at least part of the burst mode may comprise: determining an on-time for the PFC stage in the burst mode based on the output of the voltage mode controller, a DC equivalent value of an AC input voltage measurement taken prior to entering the burst mode, and an estimate of a conduction mode inductor current of the PFC stage; and modifying the DC equivalent value of the AC input voltage measurement if the output of the voltage mode controller falls outside the predetermined range.
  • modifying the DC equivalent value of the AC input voltage measurement if the output of the voltage mode controller falls outside the predetermined range may comprise: decreasing the DC equivalent value of the AC input voltage measurement if the output of the voltage mode controller is clamped at the maximum value or exceeds a target value; and increasing the DC equivalent value of the AC input voltage measurement if the output of the voltage mode controller is clamped at the minimum value or is below the target value.
  • modifying the DC equivalent value of the AC input voltage measurement if the output of the voltage mode controller falls outside the predetermined range may comprise adjusting the DC equivalent value of the AC input voltage measurement via an integrator or proportional-integral control loop, so that the output of the voltage mode controller moves towards a target value.
  • the method may further comprise: computing a delta value based on the difference between the target value and the output of the voltage mode controller; and adding the delta value to the DC equivalent value of the AC input voltage measurement.
  • the method may further comprise modifying a step size of a change made to the DC equivalent value of the AC input voltage measurement if the change exceeds a predetermined threshold.
  • FIG. 1 illustrates a block diagram of an embodiment of a switched mode power supply (SMPS) which provides load and line regulation for average current mode CCM-DCM PFC without AC input voltage measurements during burst mode operation.
  • SMPS switched mode power supply
  • FIG. 2 illustrates a block diagram of the rectification stage, the PFC stage and the digital controller of the SMPS in more detail.
  • FIG. 3 illustrates a plot diagram of an embodiment of the adaptive adjustments made by the digital controller of the SMPS in burst mode.
  • FIG. 4 illustrates a block diagram of an embodiment of the average current mode CCM PFC control technique implemented by the digital controller in steady-state operation.
  • FIG. 5 illustrates a block diagram of an embodiment of the burst mode control implemented by the digital controller for average current mode CCM PFC without AC input voltage measurements.
  • FIG. 6 illustrates a block diagram of an embodiment in which the adaptive loop implements integral or proportional-integral control.
  • the embodiments described herein provide load and line regulation for average current mode CCM-DCM PFC without AC input voltage measurements during burst mode operation in a standby mode of the power supply. By keeping the system in DCM operation as much as possible during boost mode, PFC burst mode operation is possible with a voltage control loop and without input voltage measurements and a current control loop.
  • the embodiments described herein may be implemented in digital controllers, microcontrollers, digital signal processors (DSPs), etc., and may be used to control different types of power supplies such as TV or PC power supplies with CCM PFC and LLC topologies in standby mode to meet line and load regulation requirements.
  • FIG. 1 illustrates an embodiment of a switched mode power supply (SMPS) 100 .
  • the SMPS 100 includes a rectification stage 102 such as a full wave diode rectifier bridge coupled to AC mains 104 , a PFC stage 106 coupled to the rectification stage 102 , an LLC converter 108 coupled to the PFC stage 106 , and a load 110 coupled to the LLC converter 108 .
  • the AC mains 104 may be 115V@ 60 Hz, 230V@ 50 Hz, or any other combination of voltage and frequency. In some cases, the universal voltage range of 85V to 265V AC @ 50 or 60 Hz may apply to the AC mains 104 . However, other applications such as avionics may use other frequencies.
  • the rectification stage 102 provides the same polarity of output for either polarity of the AC mains input Vin.
  • the PFC stage 106 shapes the input current of the SMPS 100 to be in synchronization with the AC mains voltage Vin, to maximize the real power drawn from the AC mains 104 .
  • the PFC stage 106 is implemented in the boost converter topology.
  • the line voltage Vin may vary from zero to a peak value of typically 375 V.
  • the PFC stage 106 includes a step-up (boost) converter for outputting a suitably high DC bus voltage (DC Bus), e.g., 380 V or more for the line voltage peak value example of 375 V.
  • DC Bus DC bus voltage
  • a boost converter has a filter inductor on the input side, which provides a smooth continuous input current waveform as opposed to the discontinuous input current of a buck or buck-boost topology.
  • the PFC stage 106 may be implemented in other converter topologies such as buck or buck-boost.
  • the LLC converter 108 coupled to the PFC stage 106 may include a switching bridge which generates a square waveform to excite an LLC resonant tank of the converter 108 .
  • the LLC resonant tank outputs a resonant sinusoidal current that is scaled and rectified by a transformer and rectifier circuit.
  • An output capacitor of the LLC converter 108 filters the rectified ac current and outputs a DC voltage (Vout) to the load 110 .
  • the SMPS 100 also includes a digital controller 112 for controlling the PFC stage 06 and the LLC converter 108 .
  • the digital controller 112 include a PFC controller 114 for the PFC stage 106 and an LLC controller 116 for the LLC converter 108 .
  • the PFC controller 114 includes a current mode (CM) controller 118 , a voltage mode (VM) controller 120 and an adaptive loop 122 .
  • the LLC controller 116 includes a CM and VM controller 124 and a burst mode controller 126 .
  • the burst mode controller 126 controls the LLC converter 108 in burst mode operation of the SMPS 100
  • the CM and VM controller 124 controls the LLC converter 108 in steady-state operation of the SMPS 100 .
  • the LLC controller 116 is the master of burst mode operation.
  • the PFC controller 114 regulates the output voltage ‘DC Bus’ of the PFC stage 106 during burst mode operation within the burst-mode timing provided by the LLC controller 116 .
  • the current mode controller 118 of the PFC controller 114 operates the PFC stage 106 in different conduction modes depending on line and load conditions in the steady-state mode.
  • the current mode controller 118 may operate the PFC stage 106 in CCM for full load/low line, by implementing a current control loop which has AC input voltage measurements as an input.
  • the current mode controller 118 may operate the PFC stage 106 in CCM+DCM within an AC half cycle in full load/high line.
  • the current mode controller 118 may operate the PFC stage 106 in full DCM at 20% load/low line.
  • CCM the current in the energy transfer inductor never goes to zero between switching cycles.
  • DCM the current goes to zero during part of the switching cycle.
  • the burst mode control implemented by the digital controller 112 is specific to the PFC stage 106 .
  • the LLC converter 108 is controlled by different control blocks in the digital controller 112 .
  • the LLC control implemented by the digital controller 112 provides the burst-on and burst-off periods to which the PFC stage 106 is to adhere.
  • the digital controller 112 controls the CCM PFC operation in burst mode with a timing constraint and provides a stable and accurate PFC output voltage regulation (DC Bus) in burst mode under a single AC input and/or under line jump conditions.
  • the digital controller 112 controls the PFC stage 106 by implementing a voltage control loop (VM) which does not have AC input voltage measurement as an input.
  • VM voltage control loop
  • the adaptive loop 122 of the PFC controller 114 modifies the voltage control loop if an output of the voltage mode controller 120 in burst mode and which is proportional to power in average current mode control falls outside a predetermined range. This way, the digital controller 112 may control the PFC stage 106 using the voltage control loop in burst mode so long as the output of the voltage mode controller 120 falls within the predetermined range.
  • FIG. 2 illustrates the digital controller 112 and the PFC stage 106 in more detail, as related to the burst mode control scheme described herein for CCM PFC without AC input voltage measurements.
  • AC mains 102 is shown connected to the rectification stage 102 by an inductor Lf and capacitor Cf.
  • the rectification stage 102 is shown as a diode bridge in this example and which includes diodes DR 1 through DR 4 connected as a full wave rectifier.
  • the PFC stage 106 is represented by an input capacitor Ci, an inductor L a switch device Q 1 such as a power MOSFET (metal-oxide semiconductor field effect transistor), IGBT (insulated gate bipolar transistor), HEMT (high-electron mobility transistor), etc.
  • MOSFET metal-oxide semiconductor field effect transistor
  • IGBT insulated gate bipolar transistor
  • HEMT high-electron mobility transistor
  • the LLC converter 108 is represented as a constant power load R L of the PFC stage 106 where capacitor Co is an output capacitor of the PFC stage 106 .
  • the LLC converter 108 is controlled separately by a separate controller 116 and separate gate drivers within the digital controller 112 , as previously described herein.
  • the digital controller 112 is a digital platform that contains multiple sense pins, multiple gate drivers, multiple DPWM (digital pulse width modulators), multiple input channel ADC (analog-to-digital converter), CPUs/ALUs (central processor units/arithmetic logic units), etc.
  • the PFC control shown in FIG. 2 is a part of the features included in the digital controller 112 . Operation of the digital controller 112 in steady-state mode and burst mode is described next in more detail with reference to FIG. 2 , as related to the burst mode control scheme described herein for CCM PFC without AC input voltage measurements.
  • the voltage control loop implemented by the voltage mode controller 120 of the PFC controller 114 is scaled by scaling unit 200 to yield an inductor current reference i L *.
  • the current control loop implemented by the current mode controller 118 of the PFC controller 114 allows the average current, which is derived from the sampled input current i L,sampled , to track the inductor current reference i L * to yield a voltage signal dVm which is used by a digital pulse width modulation (DPWM) unit 202 of the digital controller 112 to generate a duty cycle d.
  • a gate driver 204 generates a gate drive signal S for driving the switch device Q 1 of the PFC stage 106 .
  • the time instances to burst-on and burst-off are determined by the LLC control in burst mode.
  • the digital controller 112 ensures that the PFC stage 106 bursts on and bursts off synchronously with the LLC converter 108 and maintains PFC output voltage regulation.
  • the digital controller 112 has a single pin connected to a high-impedance resistor divider within the controller 112 for taking input voltage measurements.
  • the resistor divider is not shown in FIG. 2 for ease of illustration, and the single pin is schematically represented by the arrow connecting the box labelled ‘Kvg’ to the corresponding analog-to-digital converter (ADC) 206 .
  • the same pin is connected to a start-up cell within the digital controller 112 which does AC detection, and if AC power is lost during standby mode, this pin is used to discharge an external capacitor Cf to a safe voltage level, e.g., in compliance with IEC 62368-1.
  • External capacitor Cf and inductor Lf are a simplified illustration of an EMI (electromagnetic interference) filter. If the output voltage of the SMPS 100 is too low, the digital controller 112 turns on the LLC converter 108 to increase the output voltage.
  • the single pin used for AC detection and AC input voltage measurements cannot be shared because of the burst-on period which includes several switching cycles of the LLC converter 108 and the PFC stage 106 .
  • the digital controller 112 uses the pin for AC detection in standby mode, and may control the PFC stage 106 using the voltage control loop in burst mode because current loop regulation is not possible without input voltage measurements.
  • the digital controller 112 may instead have separate pins for the AC detection and AC input voltage measurement features and still employ the burst mode techniques described herein.
  • the current loop implemented by the CCM-DCM average current mode controller 118 shown in FIG. 2 is removed in burst mode.
  • the control may simplify to a single pole system in DCM where voltage mode control is sufficient and stable and there is no current control loop.
  • the voltage loop may implement constant on-time control and the PFC stage 106 may regulate at constant on time for the entire AC half cycle.
  • the SMPS 100 remains stable by keeping the PFC stage 106 in DCM as much as possible during burst mode operation, if input voltage measurements are not available, because the voltage loop simplifies to a single pole system when the PFC stage 106 is in burst mode.
  • Controlling the PFC stage 106 using the voltage control loop in burst mode with constant on-time may result in input current distortion in the case of boost PFC.
  • power factor and THD total harmonic distortion
  • the PFC stage 106 may be operated in DCM during burst mode as much as possible.
  • 100% DCM PFC operation in burst mode may not be possible.
  • DCM operation may not be possible near the peak of high line, particularly under 264 VAC where demagnetization slope of the inductor current is very gentle. The current may not drop to zero before the end of the switching period when the PFC switch device Q 1 turns on again.
  • the output v control of the voltage mode controller 120 of the PFC controller 114 is proportional to power in average current mode control.
  • the voltage mode controller 120 generates v control based on the difference v ev between a reference voltage v o * and a scaled, digitized version of the output voltage v o where Kvo represents a resistor divider ratio.
  • the minimum limit on power may correspond to a minimum value (v control,min ) of the output v control of the voltage mode controller 120 . In one embodiment, the minimum value is zero.
  • the maximum limit on power may correspond to a maximum value (v control,max ) of the output v control of the voltage mode controller 120 . The maximum limit on power may be determined by theoretical analysis of the DCM operating zone, by simulation of the SMPS 100 in burst mode with current loop and input voltage measurements, by trial and error, etc.
  • v control,max is approximately 2 times the maximum standby load, due to the transfer of power during the short burst-on period.
  • CCM operation near the peak of, e.g., 264 VAC may be expected because the demagnetization slope of the inductor current is very gentle.
  • voltage regulation remains stable.
  • the maximum power limit may be lower in burst mode than in steady-state mode.
  • the average inductor current in a switching cycle is given by:
  • v g the rectified AC input voltage
  • v control the output of the voltage control loop implemented by the voltage mode controller 120 of the PFC controller 114
  • K 1 is a constant of proportionality which balances the gain difference between the reference inductor current i L * and the sampled average inductor current i L,sampled
  • v FF is the DC equivalent value of the sampled rectified AC input voltage
  • t on is the turn-on period of the switch device Q 1 included in the PFC stage 106
  • t off is the turn-off period of the switch device Q 1 included in the PFC stage 106
  • t sw is the fixed switching period
  • L the boost inductance
  • the digital controller 112 may include analog-to-digital converter (ADC) circuitry 206 for converting analog input signals to corresponding digital values.
  • ADC analog-to-digital converter
  • the turn-on period of the switch device Q 1 included in the PFC stage 106 may be obtained.
  • the scaling unit 200 shown in FIG. 2 and used in CCM operation may be reused and modified to implement (4) for DCM operation in burst mode.
  • the initial value for v FF in burst mode is based on the last steady-state value of the input voltage measurement. That is, the initial value for v FF in burst mode may be a low-pass filtered, DC equivalent value of an AC input voltage measurement taken just prior to entering burst mode.
  • the ‘x’ input to the scaling unit 200 corresponds to a scaled version of an input voltage measurement v g where Kvg represents a resistor divider ratio.
  • K corr estimation is not possible in burst mode without input voltage or t cyc , measurements.
  • the digital controller 112 uses an assumption for K corr to keep the PFC stage 106 in DCM operation as much as possible based on the v control,max selection. Selecting a lower value of K corr causes the voltage mode controller 120 of the PFC controller 114 to regulate to a lower v control value to get the same t on . Selecting a higher value of K corr causes the voltage mode controller 120 to regulate to a higher v control value to get the same t on .
  • v control range is affected by the selection of the K corr estimate.
  • K corr may be selected based on simulation of the SMPS 100 in burst mode with current loop and input voltage measurements, by trial and error, etc.
  • the PFC stage 106 may remain in DCM operation as much as possible and burst mode operation of CCM PFC is possible with a voltage control loop and without input voltage measurements and a current control loop.
  • the digital controller 112 may also provide line regulation in standby/burst mode without AC input voltage measurements.
  • the digital controller 112 may determine the on-time t on for the switch device Q 1 of the PFC stage 106 in burst mode based on the output v control of the voltage mode controller 120 of the PFC controller 114 , the DC equivalent value v FF of an AC input voltage measurement taken prior to entering the burst mode, and an estimate K corr of the conduction mode inductor current of the PFC stage 106 .
  • the adaptive loop 122 included in or associated with the digital controller 112 may modify v FF if v control falls outside the predetermined range defined by v control,max and v control,min to account for line jumps in the AC input voltage Vin.
  • An accurate value of the DC equivalence v FF of the sampled rectified AC input voltage is difficult to obtain without AC input voltage measurements.
  • an accurate value is needed to approximate a v FF value for any number of cases of input line jumps between, e.g., 90 VAC and 264 VAC in burst mode.
  • a line jump from 264 VAC to 90 VAC in burst mode will demand a larger t on and may cause the output v control of the voltage mode controller 120 of the PFC controller 114 to clamp at the maximum value v control,max defined for burst mode, to prevent deep CCM operation.
  • the PFC output voltage may drop below a target value or even collapse.
  • v control,min e.g., zero to reduce t on and clamp at v control,min for a long period. Any small increase in the output v control of the voltage mode controller 120 when the PFC output voltage drops below a target value leads to a large change in t on . This may cause a limit cycling in the PFC output voltage, or the PFC output voltage may even collapse.
  • the digital controller 112 may approximate a v FF value required to maintain PFC output voltage regulation and to accommodate various AC input line jump cases.
  • the low-pass filter (LPF) in FIG. 2 is replaced by the adaptive loop 122 for making adjustments to v FF in burst mode.
  • FIG. 3 illustrates an embodiment of the adjustments made to v FF by the adaptive loop 122 of the PFC controller 114 in burst mode, to meet various AC input line jump cases.
  • the adaptive loop 122 decreases v FF if the output v control of the voltage mode controller 120 of the PFC controller 114 is clamped at the maximum value v control,max or exceeds a target value v control,target , and increases v FF if v control is clamped at the minimum value v control,min or falls below the target value v control,target .
  • the initial value for v FF in burst mode is based on the last steady-state value of v FF .
  • the adaptive v FF adjustment loop 122 may be enabled and performed at every sampling period T sv during the burst-on period if the output v control of the voltage mode controller 120 falls outside the predetermined range for burst mode defined by v control,max and v control,min .
  • the adaptive v FF adjustment loop 122 may be disabled once v control falls within the predetermined range for burst mode defined by v control,max and v control,min .
  • the adaptive loop 122 of the PFC controller 114 is triggered to decrease (pull down) v FF . If the actual AC input voltage Vin is higher, t on will be bigger than desired, the PFC output voltage will increase and the output v control of the voltage mode controller 120 will decrease. Once v control is clamped at v control,min which is the minimum power for burst mode and is typically zero, the adaptive loop 122 is triggered to increase (pull up) v FF .
  • the adaptive v FF adjustment loop 122 of the PFC controller 114 may be implemented as a closed-loop feedback control that adjusts the v FF value so that v control moves towards a target value v control,target .
  • the closed-loop feedback control may be hysteresis control, integral control or proportional-integral control.
  • the adaptive loop 122 may change the v FF value with a bigger step size if the change in v FF exceeds a predetermined threshold. That is, the adaptive loop 122 may decrease or increase v FF in predetermined steps and modify the step size of the change made to v FF if the change exceeds the predetermined threshold.
  • the current mode controller 118 of the PFC controller 114 may operate the PFC stage 106 in CCM using the v control and v FF values from burst mode as initial values in steady-state mode.
  • FIG. 4 illustrates an embodiment of the CCM-DCM average current mode PFC control technique implemented by the digital controller 112 in steady-state operation
  • FIG. 5 illustrates an embodiment of the burst mode control implemented by the digital controller 112 for average current mode CCM PFC without AC input voltage measurements.
  • the current mode controller 118 of the PFC controller 114 is disabled in burst mode, as schematically shown in FIG. 5 .
  • the voltage mode controller 120 of the PFC controller 114 may be the same in steady-state and burst modes, except with reduced v control,max in burst mode to keep the PFC stage 106 in DCM operation as much as possible.
  • the upper power limit v control,max may be reduced, e.g., to 20% or less of the rated load in burst mode.
  • the maximum limit v control,max on power may be determined by simulation of the SMPS 100 in burst mode with current loop and input voltage measurements, by trial and error, etc.
  • the turn-on period t on of the switch device Q 1 included in the PFC stage 106 is computed based on (5).
  • the turn-on period t on is provided to the gate driver 204 for the PFC switch device Q 1 , to set the duty cycle. From (2),
  • K 2 t onDesired ⁇ v FF 2 v control and coefficient K 2 may be determined from a system operating point (e.g. at rated load under 90 VAC).
  • K corr may be selected to be less than 1 and greater than 0. K corr may be determined based on simulation, trial and error, etc. In one embodiment, K corr is predetermined and remains unchanged during operation of the SMPS 100 in burst mode. In another embodiment, K corr may be updated, e.g., based on system learning.
  • K corr may be 0.8 based on simulation of the system in burst mode with current loop and input voltage measurements. Other values of K corr are possible and depend on the system design parameters.
  • v control,min may be set to zero
  • v control,max may be set to 20% (or higher or lower) of the rated load
  • v control,target may be set to 10% (or higher or lower) of the rated load.
  • the digital controller 112 may convert the DC equivalent value v FF of the sampled rectified AC input voltage into a digital number in decimal (d) of base 10 , by multiplying with the corresponding ADC range (an X-bit ADC gives ADC range of 2 X-1 ) and divided by the ADC voltage reference.
  • d decimal
  • ADC range an X-bit ADC gives ADC range of 2 X-1
  • the adaptive loop 122 may decrease or increase v FF in predetermined steps, as previously explained herein.
  • the adaptive loop 122 may implement hysteresis control. For example, if v control is clamped at v control,max or if v control >v control,target , the adaptive loop 122 may decrease v FF by v step1 . In a specific example, the adaptive loop 122 may decrease v FF by 1 d which represents 0.2 VAC. If v control is clamped at v control,min or if v control ⁇ v control,target , the adaptive loop 122 may increase v FF by v step1 in this example.
  • the adaptive loop 122 may change the v FF value by a larger step size if the change in v FF exceeds a certain threshold v FF,thr .
  • the adaptive loop 122 may change v FF by a larger step size if the change in v FF exceeds ⁇ 45 d which represents ⁇ 5VAC.
  • the adaptive loop 122 may decrease v FF by v step2 .
  • the adaptive loop 122 may decrease v FF by 18 d which represents 2 VAC. If v control is clamped at v control,min or if v control ⁇ v control,target , the adaptive loop 122 may increase v FF by v step2 in this example.
  • FIG. 6 illustrates an embodiment in which the adaptive loop 122 of the PFC controller 114 implements integral or proportional-integral control.
  • a feedback controller G c (z) may be an integrator (I) or a proportional-integral (PI) controller.
  • the feedback controller G c (z) adjusts v FF so that the output v control of the voltage mode controller 120 of the PFC controller 114 moves towards a target v control,target .
  • the initial value v FF,init for v FF in burst mode may be based on the last steady-state AC input voltage measurement, as previously described herein.
  • the adaptive v FF adjustment loop 122 of the PFC controller 114 is enabled and performed at every sampling period T sv during the burst-on period if v control falls outside the predetermined range for burst mode defined by v control,max and v control,min .
  • the adaptive v FF adjustment loop 122 may be disabled once v control falls within the predetermined range for burst mode defined by v control,max and v control,min .
  • the feedback controller G c (z) computes a value ⁇ v FF based on the difference between v control,target and v control , and v FF is given by the sum of v FF,init and ⁇ v FF . If, for example, v FF is higher than 280 VAC (v FF,280VAC ) or some other maximum limit, the adaptive loop 122 of the PFC controller 114 limits v FF to the maximum limit. If v FF is lower than 75VAC (v FF,75VAC ) or some other minimum limit, the adaptive loop 122 limits v FF to the minimum limit to avoid computational overflow.
  • the adaptive loop 122 may change the v FF value with a bigger step by having a larger gain in G c (z), e.g., if the change in ⁇ v FF exceeds a certain threshold v FF,thr (e.g. ⁇ 45 d which represents ⁇ 5VAC).

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TW108131551A TWI824000B (zh) 2018-10-08 2019-09-02 具ｐｆｃ叢發模式控制之開關模式電源供應器、其操作方法及數位控制器
KR1020190123869A KR20200040673A (ko) 2018-10-08 2019-10-07 Pfc 버스트 모드 제어 기능이 있는 스위치 모드 전원 공급 장치
CN201910949140.6A CN111010026A (zh) 2018-10-08 2019-10-08 用于电源的数字控制器、电源及操作电源的方法

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