TWI765740B - Symmetrical switching type high boost dc converter - Google Patents

Symmetrical switching type high boost dc converter Download PDF

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TWI765740B
TWI765740B TW110121010A TW110121010A TWI765740B TW I765740 B TWI765740 B TW I765740B TW 110121010 A TW110121010 A TW 110121010A TW 110121010 A TW110121010 A TW 110121010A TW I765740 B TWI765740 B TW I765740B
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converter
diode
capacitor
boost
voltage
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TW202249406A (en
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楊松霈
陳信助
黃昭明
湯曜誠
吳宗育
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崑山科技大學
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Abstract

This invention relates to a symmetrical switching type high boost DC converter, which is mainly used in renewable energy, and has both switching inductor boost function and coupled inductor multiplier module boost function, so that the boost ratio of the converter has the transformer turns ratio n, and achieves high power application, high boost gain and high conversion efficiency, and increases the practical efficiency in its overall implementation.

Description

對稱切換型高升壓直流轉換器Symmetrically Switched High Boost DC Converter

本發明係有關於一種對稱切換型高升壓直流轉換器，尤其是指一種應用於再生能源，其同時具有切換式電感升壓功能及耦合電感倍增模組升壓功能，可使轉換器的升壓比具有變壓器匝數比n，達到高功率應用、高升壓增益及高轉換效率，而在其整體施行使用上更增實用功效特性者。The present invention relates to a symmetrical switching type high-boost DC converter, in particular to a regenerative energy source, which has both a switching inductance boosting function and a coupled inductance multiplying module boosting function, so that the boosting of the converter can be improved. The voltage ratio has the transformer turns ratio n, which achieves high power applications, high boost gain and high conversion efficiency, and enhances utility characteristics in its overall implementation.

按，地球升溫情況加劇使地球氣候異常變化嚴重，世界各國均開始積極審視眼前這嚴重的問題，因此，從1997年12月有38個國家及歐盟在日本簽署「京都議定書」開始，中間經2015年法國巴黎舉行的第21屆聯合國氣候變化會議［COP 21］，通過歷史性的「巴黎協定」，195個與會國家一致同意控制溫室氣體的排放及至工業化至2100年前全球升溫不超過攝氏2度且努力控制於1.5度內，再到2018年於波蘭舉辦的第24屆聯合國氣候變化會議［COP 24］，均不斷確保各國碳減排的國際標準與減碳目標。隨著太陽能與風力發電技術提升與成本漸降，再生能源的發電技術開發與電源轉換的高效率技術是未來科技發展必然的趨勢，如此，可避免石化能源過度使用，以減少二氧化碳排放量。According to the fact that the increase in the temperature of the earth has caused serious changes in the earth's climate, all countries in the world have begun to actively examine this serious problem. Therefore, from December 1997, 38 countries and the European Union signed the "Kyoto Protocol" in Japan, and in the middle of 2015 At the 21st United Nations Climate Change Conference [COP 21] held in Paris, France, through the historic "Paris Agreement", 195 participating countries unanimously agreed to control greenhouse gas emissions and to industrialize until 2100. Global warming does not exceed 2 degrees Celsius And efforts are made to control it within 1.5 degrees, and then to the 24th United Nations Climate Change Conference [COP 24] held in Poland in 2018, all countries will continue to ensure international standards and carbon reduction targets for carbon reduction. With the improvement of solar and wind power generation technology and the gradual cost reduction, the development of renewable energy power generation technology and the high-efficiency technology of power conversion are the inevitable trends of future technological development. In this way, excessive use of fossil energy can be avoided and carbon dioxide emissions can be reduced.

再生能源或綠色能源方面，常見有太陽能、潮汐能、風力能、水力能、生質能、地熱能與燃料電池等，在這些再生能源中以太陽能及燃料電池發電系統的技術在分散式之直流發電系統中，最常被應用與討論。再生能源分散式發電電力系統係包含太陽能組件、燃料電池組件、高升壓直流轉換器［high step-up dc-dc converter］、逆變器［inverter，dc-dc power converter］及負載或電網。以太陽能發電系統而言，太陽能陣列將光能轉換為電能，而每個太陽能陣列可透過數個太陽能模組串聯或並聯所組成，但是太陽能陣列串聯過多會造成晶格不匹配［lattice mismatch］，或因無法避免遮蔽效應影響，因此限制了太陽能陣列的輸出電壓，通常低於50V，所以該系統需要具有高升壓轉換器以匯入高直流排電壓400V，以作為後級DC-AC變頻器的高直流輸入電壓，再由變頻器輸出功率給AC負載［如馬達］或與市電並聯，因此，高升壓轉換器在分散式發電系統中扮演著很重要的角色。In terms of renewable energy or green energy, solar energy, tidal energy, wind energy, hydraulic energy, biomass energy, geothermal energy and fuel cells are common. In the power generation system, it is most often used and discussed. The renewable energy distributed power generation system includes solar modules, fuel cell modules, high step-up dc-dc converters, inverters (inverters, dc-dc power converters), and loads or grids. For solar power generation systems, solar arrays convert light energy into electrical energy, and each solar array can be composed of several solar modules in series or in parallel, but too many solar arrays in series will cause lattice mismatch. Or because the shading effect cannot be avoided, the output voltage of the solar array is limited, which is usually lower than 50V, so the system needs to have a high boost converter to sink the high DC voltage of 400V as a downstream DC-AC inverter The high DC input voltage of the inverter is then used to output power to the AC load (such as a motor) or in parallel with the mains. Therefore, the high boost converter plays an important role in the distributed power generation system.

在分散式發電系統中，太陽能發電及燃料電池是最重要的再生能源之一，但是在居家應用中，為了使用環境的安全以及可靠度，再生能源的輸出側一般都是低直流電壓，通常低於40V dc，為了後續併網發電或連接至直流微電網的需求，先透過升壓型轉換器提升低電壓至高電壓直流匯流排，通常提升電壓約10倍左右，以產生變頻器［DC-AC Inverter］所需要的高直流電壓。應用再生能源之電力系統，例如：對一個單相交流220V的電網系統而言，此高電壓直流匯流排通常為380V~400V，以利DC-AC後端變頻器的負載應用或併聯市電使用。 In distributed power generation systems, solar power generation and fuel cells are one of the most important renewable energy sources, but in home applications, for the safety and reliability of the use environment, the output side of renewable energy is generally low DC voltage, usually low At 40V dc , for the subsequent grid-connected power generation or connection to the DC micro-grid, the low-voltage to high-voltage DC busbar is firstly upgraded through a boost converter, usually about 10 times, to generate an inverter [DC-AC Inverter] required high DC voltage. Power systems using renewable energy, for example, for a single-phase AC 220V power grid system, the high-voltage DC busbar is usually 380V~400V, which is convenient for the load application of DC-AC back-end inverters or the use of parallel mains.

然而，由上述高升壓技術可知，傳統切換電感升壓式技術雖可達到電路簡單，能提升轉換器之電壓轉換比的預期功效，但也在其實際施行使用上發現，該技術並無法再進一步提升轉換器升壓比；另，耦合電感升壓式技術則係因為電路拓樸本身限制，而無法具有切換電感的升壓功能，致令其在整體電路設計上仍存在有改進之空間。However, it can be seen from the above high boosting technology that although the traditional switching inductor boosting technology can achieve the expected effect of simple circuit and can improve the voltage conversion ratio of the converter, it is also found in its actual implementation that this technology can no longer be used. The boost ratio of the converter is further improved; in addition, the coupled inductor boost technology cannot have the boost function of switching inductors due to the limitation of the circuit topology itself, so there is still room for improvement in the overall circuit design.

緣是，發明人有鑑於此，秉持多年該相關行業之豐富設計開發及實際製作經驗，針對現有之結構及缺失再予以研究改良，提供一種對稱切換型高升壓直流轉換器，以期達到更佳實用價值性之目的者。The reason is that, in view of this, the inventor, adhering to years of rich experience in design, development and actual production in the related industry, researches and improves the existing structure and defects, and provides a symmetrical switching type high-boost DC converter, in order to achieve a better The purpose of practical value.

本發明之主要目的在於提供一種對稱切換型高升壓直流轉換器，主要係應用於再生能源，其同時具有切換式電感升壓功能及耦合電感倍增模組升壓功能，可使轉換器的升壓比具有變壓器匝數比n，達到高功率應用、高升壓增益及高轉換效率，而在其整體施行使用上更增實用功效特性者。The main purpose of the present invention is to provide a symmetrical switching type high-boost DC converter, which is mainly used in renewable energy sources, and has both a switching inductance boosting function and a coupled inductance multiplication module boosting function, which can increase the boosting of the converter. The voltage ratio has the transformer turns ratio n, which achieves high power applications, high boost gain and high conversion efficiency, and enhances utility characteristics in its overall implementation.

為令本發明所運用之技術內容、發明目的及其達成之功效有更完整且清楚的揭露，茲於下詳細說明之，並請一併參閱所揭之圖式及圖號：In order to make the technical content used in the present invention, the purpose of the invention and the effect achieved by the present invention more completely and clearly disclosed, it is explained in detail below, and please refer to the disclosed drawings and drawing numbers together:

首先，請參閱第一圖本發明之電路圖所示，本發明之轉換器(1)主要係於輸入電壓

Figure 02_image001
之正極分別連接第一電容
Figure 02_image003
之正極、第一功率開關
Figure 02_image015
之第一端及第一耦合電感一次側
Figure 02_image019
之第一端，該第一耦合電感一次側
Figure 02_image051
形成有第一磁化電感
Figure 02_image023
，該輸入電壓
Figure 02_image001
之負極分別連接第二電容
Figure 02_image005
之負極、第二功率開關
Figure 02_image017
之第二端及第二耦合電感一次側
Figure 02_image025
之第一端，該第二耦合電感一次側
Figure 02_image053
形成有第二磁化電感
Figure 02_image029
，該第一電容
Figure 02_image003
之負極分別連接該第二電容
Figure 02_image005
之正極、第三電容
Figure 02_image007
之負極及第四電容
Figure 02_image009
之正極，該第一功率開關
Figure 02_image015
之第二端分別連接該第二耦合電感一次側
Figure 02_image025
之第二端及第四二極體
Figure 02_image039
之負極，該第一耦合電感一次側
Figure 02_image019
之第二端分別連接該第二功率開關
Figure 02_image017
之第一端及第三二極體
Figure 02_image037
之正極，該第三二極體
Figure 02_image037
之負極分別連接該第三電容
Figure 02_image007
之正極、第六電容
Figure 02_image013
之負極及第二二極體
Figure 02_image035
之正極，該第六電容
Figure 02_image013
之正極分別連接第五電容
Figure 02_image011
之負極及第二耦合電感二次側
Figure 02_image027
之第二端，且於該第六電容
Figure 02_image013
之正極與該第二耦合電感二次側
Figure 02_image054
之第二端之間形成有漏電感
Figure 02_image031
，該第二二極體
Figure 02_image035
之負極分別連接第一耦合電感二次側
Figure 02_image021
之第二端及第一二極體
Figure 02_image033
之正極，該第一耦合電感二次側
Figure 02_image055
之第一端與該第二耦合電感二次側
Figure 02_image054
之第一端相連接，該第一二極體
Figure 02_image056
之負極分別連接該第五電容
Figure 02_image011
之正極及負載
Figure 02_image041
之第一端，該負載
Figure 02_image041
之第二端則分別連接該第四電容
Figure 02_image009
之負極及該第四二極體
Figure 02_image039
之正極。 First of all, please refer to the circuit diagram of the present invention as shown in the first figure, the converter (1) of the present invention is mainly related to the input voltage
Figure 02_image001
The positive poles are respectively connected to the first capacitor
Figure 02_image003
The positive pole, the first power switch
Figure 02_image015
the first end and the primary side of the first coupled inductor
Figure 02_image019
the first end, the primary side of the first coupled inductor
Figure 02_image051
A first magnetizing inductance is formed
Figure 02_image023
, the input voltage
Figure 02_image001
The negative poles are respectively connected to the second capacitor
Figure 02_image005
The negative pole, the second power switch
Figure 02_image017
the second end and the primary side of the second coupled inductor
Figure 02_image025
the first end of the second coupled inductor primary side
Figure 02_image053
A second magnetizing inductance is formed
Figure 02_image029
, the first capacitor
Figure 02_image003
The negative poles are respectively connected to the second capacitor
Figure 02_image005
The positive electrode, the third capacitor
Figure 02_image007
The negative electrode and the fourth capacitor
Figure 02_image009
the positive pole of the first power switch
Figure 02_image015
The second ends are respectively connected to the primary side of the second coupled inductor
Figure 02_image025
the second end and the fourth diode
Figure 02_image039
the negative pole, the primary side of the first coupled inductor
Figure 02_image019
The second ends are respectively connected to the second power switch
Figure 02_image017
the first terminal and the third diode
Figure 02_image037
the positive electrode, the third diode
Figure 02_image037
The negative poles are respectively connected to the third capacitor
Figure 02_image007
The positive electrode, the sixth capacitor
Figure 02_image013
The negative electrode and the second diode
Figure 02_image035
the positive pole, the sixth capacitor
Figure 02_image013
The positive poles are respectively connected to the fifth capacitor
Figure 02_image011
the negative pole and the secondary side of the second coupled inductor
Figure 02_image027
the second end of the sixth capacitor
Figure 02_image013
the positive pole and the secondary side of the second coupled inductor
Figure 02_image054
A leakage inductance is formed between the second ends of
Figure 02_image031
, the second diode
Figure 02_image035
The negative poles are respectively connected to the secondary side of the first coupling inductor
Figure 02_image021
the second terminal and the first diode
Figure 02_image033
the positive pole, the secondary side of the first coupled inductor
Figure 02_image055
the first end and the secondary side of the second coupled inductor
Figure 02_image054
connected to the first end of the first diode
Figure 02_image056
The negative poles are respectively connected to the fifth capacitor
Figure 02_image011
positive and load
Figure 02_image041
the first end of the load
Figure 02_image041
The second terminals are respectively connected to the fourth capacitor
Figure 02_image009
the negative electrode and the fourth diode
Figure 02_image039
the positive pole.

而對該轉換器(1)之電路動作原理作簡易分析，以確定該轉換器(1)之高升壓性能；假設：And a simple analysis of the circuit operation principle of the converter (1) is carried out to determine the high boost performance of the converter (1); it is assumed that:

1.第一功率開關

Figure 02_image015
與第二功率開關
Figure 02_image017
以交錯式驅動。 1. The first power switch
Figure 02_image015
with second power switch
Figure 02_image017
Drive in a staggered manner.

2.轉換器(1)操作於連續導通模式［CCM］。2. The converter (1) operates in continuous conduction mode [CCM].

3.轉換器(1)已達到穩態。3. Converter (1) has reached steady state.

4.電路中所有開關及二極體皆為理想元件。4. All switches and diodes in the circuit are ideal components.

5.電路中所有電感以及電容皆為理想元件，不具有寄生阻抗。5. All inductors and capacitors in the circuit are ideal components without parasitic impedance.

6.各電容相當大，可忽略電壓漣波，使得電容電壓為常數，故電容電壓可視為電壓源，輸出電壓視

Figure 02_image057
為常數。 6. Each capacitor is quite large, and the voltage ripple can be ignored, so that the capacitor voltage is constant, so the capacitor voltage can be regarded as a voltage source, and the output voltage depends on the output voltage.
Figure 02_image057
is a constant.

且根據各開關切換和各二極體導通與否，可以將該轉換器(1)在一個切換週期的動作，分成四個線性階段，在一個切換週期

Figure 02_image059
的電力轉換器之時序及波形，請再一併參閱第二圖本發明之時序圖所示： And according to the switching of each switch and the conduction of each diode, the action of the converter (1) in one switching cycle can be divided into four linear stages, and in one switching cycle
Figure 02_image059
For the timing and waveform of the power converter, please also refer to the second diagram of the timing diagram of the present invention:

預備階段［

Figure 02_image061
］：［第一功率開關
Figure 02_image063
：ON、第二功率開關
Figure 02_image064
：ON、第一二極體
Figure 02_image066
：OFF、第二二極體
Figure 02_image068
：ON、第三二極體
Figure 02_image070
：OFF、第四二極體
Figure 02_image072
：OFF］：請再一併參閱第三圖本發明之預備階段等效線性電路圖所示，在預備階段時，該第一功率開關
Figure 02_image063
與該第二功率開關
Figure 02_image064
導通［ON］持續一段時間，該第一二極體
Figure 02_image066
、該第三二極體
Figure 02_image070
、該第四二極體
Figure 02_image072
皆因逆向偏壓而OFF，此時該第一磁化電感
Figure 02_image023
、該第二磁化電感
Figure 02_image029
因跨該輸入電壓
Figure 02_image001
，則電流以斜率
Figure 02_image074
、
Figure 02_image076
線性上升。當該第一功率開關
Figure 02_image063
由ON切換至OFF時，該第二二極體
Figure 02_image068
由ON切換至OFF，該第一二極體
Figure 02_image066
、該第四二極體
Figure 02_image072
由OFF切換至ON，則該轉換器(1)進入在一個切換週期
Figure 02_image059
下之第一階段電路動作。 preparatory stage
Figure 02_image061
]: [First power switch
Figure 02_image063
: ON, second power switch
Figure 02_image064
: ON, first diode
Figure 02_image066
: OFF, second diode
Figure 02_image068
: ON, third diode
Figure 02_image070
: OFF, fourth diode
Figure 02_image072
: OFF]: Please also refer to Figure 3, as shown in the equivalent linear circuit diagram of the preliminary stage of the present invention, in the preliminary stage, the first power switch
Figure 02_image063
with this second power switch
Figure 02_image064
Conduction [ON] continues for a period of time, the first diode
Figure 02_image066
, the third diode
Figure 02_image070
, the fourth diode
Figure 02_image072
are all turned OFF due to reverse bias, at this time the first magnetizing inductance
Figure 02_image023
, the second magnetizing inductance
Figure 02_image029
due to the input voltage across this
Figure 02_image001
, then the current slopes
Figure 02_image074
,
Figure 02_image076
rise linearly. When the first power switch
Figure 02_image063
When switching from ON to OFF, the second diode
Figure 02_image068
switched from ON to OFF, the first diode
Figure 02_image066
, the fourth diode
Figure 02_image072
switched from OFF to ON, the converter (1) enters in a switching cycle
Figure 02_image059
The following first stage circuit operation.

第一階段［

Figure 02_image078
］：［第一功率開關
Figure 02_image063
：OFF、第二功率開關
Figure 02_image064
：ON、第一二極體
Figure 02_image066
：ON、第二二極體
Figure 02_image068
：OFF、第三二極體
Figure 02_image070
：OFF、第四二極體
Figure 02_image072
：ON］：請再一併參閱第四圖本發明之第一階段等效線性電路圖所示，該第一功率開關
Figure 02_image063
已由ON切換至OFF，該第二二極體
Figure 02_image068
由ON切換至OFF，該第一二極體
Figure 02_image066
、該第四二極體
Figure 02_image072
由OFF切換至ON，該第二功率開關
Figure 02_image064
保持為ON，此時該第一磁化電感
Figure 02_image023
因跨該輸入電壓
Figure 02_image001
，則電流以斜率
Figure 02_image074
線性上升，第二磁化電感電流
Figure 02_image080
以斜率
Figure 02_image082
線性下降，當該第一功率開關
Figure 02_image063
由OFF切換至ON，而該第二二極體
Figure 02_image068
由OFF切換至ON，該第一二極體
Figure 02_image066
、該第四二極體
Figure 02_image072
由ON切換至OFF時，則該轉換器(1)進入在一個切換週期
Figure 02_image059
下之第二階段電路動作。 The first stage[
Figure 02_image078
]: [First power switch
Figure 02_image063
: OFF, second power switch
Figure 02_image064
: ON, first diode
Figure 02_image066
: ON, second diode
Figure 02_image068
: OFF, third diode
Figure 02_image070
: OFF, fourth diode
Figure 02_image072
:ON]: Please also refer to the fourth figure of the first-stage equivalent linear circuit diagram of the present invention, the first power switch
Figure 02_image063
has been switched from ON to OFF, the second diode
Figure 02_image068
switched from ON to OFF, the first diode
Figure 02_image066
, the fourth diode
Figure 02_image072
switched from OFF to ON, the second power switch
Figure 02_image064
remains ON, at this time the first magnetizing inductance
Figure 02_image023
due to the input voltage across this
Figure 02_image001
, then the current slopes
Figure 02_image074
rising linearly, the second magnetizing inductor current
Figure 02_image080
with slope
Figure 02_image082
drops linearly when the first power switch
Figure 02_image063
switched from OFF to ON, and the second diode
Figure 02_image068
switched from OFF to ON, the first diode
Figure 02_image066
, the fourth diode
Figure 02_image072
When switching from ON to OFF, the converter (1) enters a switching cycle in
Figure 02_image059
The following second stage circuit operation.

第二階段［

Figure 02_image084
］：［第一功率開關
Figure 02_image063
：ON、第二功率開關
Figure 02_image064
：ON、第一二極體
Figure 02_image066
：OFF、第二二極體
Figure 02_image068
：ON、第三二極體
Figure 02_image070
：OFF、第四二極體
Figure 02_image072
：OFF］：請再一併參閱第五圖本發明之第二階段等效線性電路圖所示，本階段該第一功率開關
Figure 02_image063
由OFF切換至ON，該第二功率開關
Figure 02_image064
保持為ON，而該第二二極體
Figure 02_image068
由OFF切換至ON，該第一二極體
Figure 02_image066
、該第四二極體
Figure 02_image072
由ON切換至OFF，此時電路動作與預備階段相同；當該第二功率開關
Figure 02_image064
由ON切換至OFF時，則該轉換器(1)進入在一個切換週期
Figure 02_image059
下之第三階段電路動作。 second stage[
Figure 02_image084
]: [First power switch
Figure 02_image063
: ON, second power switch
Figure 02_image064
: ON, first diode
Figure 02_image066
: OFF, second diode
Figure 02_image068
: ON, third diode
Figure 02_image070
: OFF, fourth diode
Figure 02_image072
: OFF]: Please also refer to the second-stage equivalent linear circuit diagram of the present invention in Fig. 5, the first power switch in this stage
Figure 02_image063
switched from OFF to ON, the second power switch
Figure 02_image064
remains ON while the second diode
Figure 02_image068
switched from OFF to ON, the first diode
Figure 02_image066
, the fourth diode
Figure 02_image072
From ON to OFF, the circuit action is the same as the preparatory stage; when the second power switch
Figure 02_image064
When switching from ON to OFF, the converter (1) enters a switching cycle in
Figure 02_image059
The third stage circuit action below.

第三階段［

Figure 02_image086
］：［第一功率開關
Figure 02_image063
：ON、第二功率開關
Figure 02_image064
：OFF、第一二極體
Figure 02_image066
：ON、第二二極體
Figure 02_image068
：OFF、第三二極體
Figure 02_image070
：ON、第四二極體
Figure 02_image072
：OFF］：請再一併參閱第六圖本發明之第三階段等效線性電路圖所示，該第二功率開關
Figure 02_image064
已由ON轉變為OFF，則該第二二極體
Figure 02_image068
由ON切換至OFF，此時該第一二極體
Figure 02_image066
、該第三二極體
Figure 02_image070
由OFF切換至ON，該第一功率開關
Figure 02_image063
保持為ON，此時該第二磁化電感
Figure 02_image029
因跨該輸入電壓
Figure 02_image001
，電流以斜率
Figure 02_image088
線性上升，則第一磁化電感電流
Figure 02_image089
以斜率
Figure 02_image091
線性下降，當該第一功率開關
Figure 02_image063
由OFF切換至ON，而該第二二極體
Figure 02_image068
由OFF切換至ON，該第一二極體
Figure 02_image066
、該第三二極體
Figure 02_image093
由ON切換至OFF時，則該轉換器(1)進入在一個切換週期
Figure 02_image059
下之第四階段電路動作。 The third phase[
Figure 02_image086
]: [First power switch
Figure 02_image063
: ON, second power switch
Figure 02_image064
: OFF, first diode
Figure 02_image066
: ON, second diode
Figure 02_image068
: OFF, third diode
Figure 02_image070
: ON, fourth diode
Figure 02_image072
: OFF]: Please also refer to the third-stage equivalent linear circuit diagram of the present invention in Fig. 6, the second power switch
Figure 02_image064
has been turned from ON to OFF, the second diode
Figure 02_image068
switch from ON to OFF, at this time the first diode
Figure 02_image066
, the third diode
Figure 02_image070
switched from OFF to ON, the first power switch
Figure 02_image063
remains ON, at this time the second magnetizing inductance
Figure 02_image029
due to the input voltage across this
Figure 02_image001
, the current with a slope
Figure 02_image088
rises linearly, the first magnetizing inductor current
Figure 02_image089
with slope
Figure 02_image091
drops linearly when the first power switch
Figure 02_image063
switched from OFF to ON, and the second diode
Figure 02_image068
switched from OFF to ON, the first diode
Figure 02_image066
, the third diode
Figure 02_image093
When switching from ON to OFF, the converter (1) enters a switching cycle in
Figure 02_image059
The fourth stage circuit action below.

第四階段［

Figure 02_image094
］：［第一功率開關
Figure 02_image063
：ON、第二功率開關
Figure 02_image064
：ON、第一二極體
Figure 02_image066
：OFF、第二二極體
Figure 02_image068
：ON、第三二極體
Figure 02_image070
：OFF、第四二極體
Figure 02_image072
：OFF］：請再一併參閱第七圖本發明之第四階段等效線性電路圖所示，本階段該第二功率開關
Figure 02_image064
由OFF切換至ON，該第一功率開關
Figure 02_image063
保持為ON，而該第二二極體
Figure 02_image068
由OFF切換至ON，該第一二極體
Figure 02_image066
、該第三二極體
Figure 02_image096
由ON切換至OFF，此時電路動作與預備階段相同；當該第一功率開關
Figure 02_image063
由ON切換至OFF時，則該轉換器(1)進入下一階段，完成一個切換週期
Figure 02_image059
下之電路動作。 the fourth stage
Figure 02_image094
]: [First power switch
Figure 02_image063
: ON, second power switch
Figure 02_image064
: ON, first diode
Figure 02_image066
: OFF, second diode
Figure 02_image068
: ON, third diode
Figure 02_image070
: OFF, fourth diode
Figure 02_image072
: OFF]: Please refer to Figure 7, which is the equivalent linear circuit diagram of the fourth stage of the present invention, the second power switch in this stage.
Figure 02_image064
switched from OFF to ON, the first power switch
Figure 02_image063
remains ON while the second diode
Figure 02_image068
switched from OFF to ON, the first diode
Figure 02_image066
, the third diode
Figure 02_image096
From ON to OFF, the circuit action is the same as the preparatory stage; when the first power switch
Figure 02_image063
When switching from ON to OFF, the converter (1) enters the next stage and completes a switching cycle
Figure 02_image059
The following circuit operates.

而依據上述電路動作分析，該轉換器(1)即可能到電壓轉換比：And according to the above circuit action analysis, the converter (1) is possible to the voltage conversion ratio:

Figure 02_image097
Figure 02_image097

另，以元件試誤法驗證所提出之數據及參數及電氣規格，請參下表1所示，使用IsSpice模擬軟體［請再一併參閱第八圖本發明之模擬電路示意圖所示］，再以模擬結果驗證：輸入電壓

Figure 02_image001
、輸出電壓
Figure 02_image099
、導通比D之關係，以確認該轉換器(1)之高升壓比之性能，也同時確認該轉換器(1)之電路動作正確性。 輸入電壓
Figure 02_image001
 40 V 耦合電感
Figure 02_image100
、
Figure 02_image102
 280 μH 輸出電壓
Figure 02_image099
 400 V 電容
Figure 02_image104
、
Figure 02_image106
 1000 μF 輸出功率
Figure 02_image108
 500 W 電容
Figure 02_image110
、
Figure 02_image112
、
Figure 02_image114
、
Figure 02_image116
 560 μF 切換頻率
Figure 02_image118
 50 kHz 導通比 D 0.735 表1  電氣規格與元件參數 In addition, verify the proposed data, parameters and electrical specifications by the component trial and error method, please refer to the table 1 below, use the IsSpice simulation software [please refer to the schematic diagram of the simulation circuit of the present invention in Figure 8], and then use the IsSpice simulation software. Verified with Simulation Results: Input Voltage
Figure 02_image001
,The output voltage
Figure 02_image099
, the relationship between the conduction ratio D, to confirm the performance of the high boost ratio of the converter (1), and also to confirm the correctness of the circuit operation of the converter (1). Input voltage
Figure 02_image001
Figure 02_image001
 40V coupled inductance
Figure 02_image100
,
Figure 02_image102
 280 μH The output voltage
Figure 02_image099
Figure 02_image099
 400V capacitance
Figure 02_image104
,
Figure 02_image106
 1000 μF Output Power
Figure 02_image108
 500W capacitance
Figure 02_image110
,
Figure 02_image112
,
Figure 02_image114
,
Figure 02_image116
 560 μF switching frequency
Figure 02_image118
 50kHz Conduction ratio D 0.735 Table 1 Electrical Specifications and Component Parameters

模擬結果如下：The simulation results are as follows:

1.該轉換器(1)以交錯式切換操作之電氣規格驗證：1. The converter (1) is verified with electrical specifications for staggered switching operation:

輸入電壓

Figure 02_image120
、輸出電壓
Figure 02_image099
、導通比D，由電壓轉換比可算得當輸入電壓
Figure 02_image120
、輸出電壓
Figure 02_image122
之導通比D的理論值為0.64，請再一併參閱第九圖本發明之開關驅動信號
Figure 02_image043
、
Figure 02_image045
與輸入電壓
Figure 02_image047
及輸出電壓
Figure 02_image049
的模擬波形圖［交錯式切換操作］所示，由該第九圖可知，輸入電壓
Figure 02_image120
、輸出電壓
Figure 02_image122
時，導通比D的模擬值為0.74，其數值比理論值大許多，需進一步回歸分析探討升壓性能，否則轉換效率會不佳。 Input voltage
Figure 02_image120
,The output voltage
Figure 02_image099
, the conduction ratio D, the input voltage can be calculated from the voltage conversion ratio
Figure 02_image120
,The output voltage
Figure 02_image122
The theoretical value of the conduction ratio D is 0.64, please refer to the switch driving signal of the present invention in Figure 9.
Figure 02_image043
,
Figure 02_image045
with input voltage
Figure 02_image047
and output voltage
Figure 02_image049
As shown in the analog waveform diagram of [Interleaved Switching Operation], it can be seen from this ninth diagram that the input voltage
Figure 02_image120
,The output voltage
Figure 02_image122
When , the analog value of the conduction ratio D is 0.74, which is much larger than the theoretical value. Further regression analysis is required to discuss the boost performance, otherwise the conversion efficiency will be poor.

2.該轉換器(1)以同步式切換操作之電氣規格驗證：2. The converter (1) is verified with electrical specifications for synchronous switching operation:

輸入電壓

Figure 02_image120
、輸出電壓
Figure 02_image099
、導通比D，由電壓轉換比可算得當輸入電壓
Figure 02_image120
、輸出電壓
Figure 02_image122
之導通比D的理論值為0.64，請再一併參閱第十圖本發明之開關驅動信號
Figure 02_image043
、
Figure 02_image045
與輸入電壓
Figure 02_image047
及輸出電壓
Figure 02_image049
的模擬波形圖［同步式切換操作］所示，由該第十圖可知，輸入電壓
Figure 02_image120
、輸出電壓
Figure 02_image122
時，導通比D的模擬值為0.65，其數值比理論值略大，這代表同步切換操作會具有佳的升壓性能和轉換效率。 Input voltage
Figure 02_image120
,The output voltage
Figure 02_image099
, the conduction ratio D, the input voltage can be calculated from the voltage conversion ratio
Figure 02_image120
,The output voltage
Figure 02_image122
The theoretical value of the conduction ratio D is 0.64. Please refer to the switch driving signal of the present invention in Figure 10.
Figure 02_image043
,
Figure 02_image045
with input voltage
Figure 02_image047
and output voltage
Figure 02_image049
As shown in the analog waveform diagram of [Synchronous switching operation], it can be seen from the tenth diagram that the input voltage
Figure 02_image120
,The output voltage
Figure 02_image122
When , the analog value of the conduction ratio D is 0.65, which is slightly larger than the theoretical value, which means that the synchronous switching operation will have good boost performance and conversion efficiency.

而該轉換器(1)與相關文獻所發表之高升壓轉換器相比，具有較佳的高升壓轉換比及優勢，以下就該轉換器(1)與相關文中之高升壓轉換器，在電壓轉換比、開關應力、二極體數量及耦合電感繞組數做比較，詳細比較分項敘述如下［請再一併參閱下表2所示］：The converter (1) has better high boost conversion ratio and advantages compared with the high boost converters published in related literatures. The following describes the converter (1) and the high boost converters in related literatures. , compare the voltage conversion ratio, switching stress, the number of diodes and the number of coupled inductor windings. The detailed comparison is described as follows [please refer to Table 2 below]:

1.責任導通比比較：本發明之該轉換器(1)的電壓轉換比並無限制，而文獻［2］及［3］所提出之高升壓轉換器，由於要滿足上下均有升壓式轉換器之電路動作特性，故必須操作在D＞0.5。因此，本發明之該轉換器(1)具有較大的工作應用範圍。1. Comparison of duty conduction ratio: the voltage conversion ratio of the converter (1) of the present invention is not limited, and the high boost converters proposed in the literature [2] and [3] have to meet the requirements of boosting both up and down. The circuit action characteristics of the converter must be operated at D>0.5. Therefore, the converter (1) of the present invention has a wider working application range.

2.電壓轉換比：請再一併參閱第十一圖本發明於匝數比n=1時之電壓轉換比比較曲線圖所示，本發明之該轉換器(1)在匝數比n=1時，其電壓增益雖略低於文獻［2］之轉換器，但其並無導通比的限制，且在n=3時，請再一併參閱第十二圖本發明於匝數比n=3時之電壓轉換比比較曲線圖所示，本發明之該轉換器(1)僅需操作在D=0.28則升壓比達10倍時，而文獻［2］雖升壓比高，但卻無法在D＜0.5下操作，故無法達成10倍升壓。此外，本發明之該轉換器(1)在相同電氣條件，其電壓增益均大於文獻［1］傳統切換式電感高升壓轉換器，在n=3時，兩者電壓增益差距更是大。2. Voltage conversion ratio: Please refer to Figure 11. The voltage conversion ratio of the present invention when the turns ratio n=1 is shown in the comparison graph. The converter (1) of the present invention is at the turns ratio n=1 1, the voltage gain is slightly lower than that of the converter in the literature [2], but there is no restriction on the conduction ratio, and when n=3, please refer to the twelfth figure again. As shown in the comparison graph of the voltage conversion ratio when D = 3, the converter (1) of the present invention only needs to operate at D = 0.28 and the boost ratio is 10 times. However, it cannot operate under D<0.5, so it cannot achieve a 10-fold boost. In addition, under the same electrical conditions, the voltage gain of the converter (1) of the present invention is greater than that of the traditional switching inductance high boost converter in reference [1]. When n=3, the difference between the voltage gains is even greater.

3.開關電壓應力：本發明之該轉換器(1)在匝比n=1條件下，該轉換器(1)的開關應力小於輸出電壓的1/4，雖在D＞0.5時略大於文獻［3］轉換器之開關應力，但是其電路架構卻相對於文獻［3］簡單許多。3. Switching voltage stress: under the condition of the turns ratio n=1 of the converter (1) of the present invention, the switching stress of the converter (1) is less than 1/4 of the output voltage, although it is slightly larger than the literature when D>0.5 [3] The switching stress of the converter, but its circuit structure is much simpler than the literature [3].

4.電感繞組做比較：本發明之該轉換器(1)及文獻［2］，其電壓增益小於文獻［3］之轉換器，主要就是在於耦合電感繞組數少2組之原因。 高升壓 轉換器 傳統升壓式轉換器 文獻［1］ 文獻［2］ 文獻［3］ 本發明 電壓 轉換比

Figure 02_image124
Figure 02_image126
Figure 02_image128
Figure 02_image130
Figure 02_image132
 開關應力 以n=1表示
Figure 02_image134
Figure 02_image134
Figure 02_image135
Figure 02_image137
Figure 02_image139
 關關數量 1 2 2 2 2 二極體數量 1 1 4 8 4 導通比限制 無 無 D＞0.5 D＞0.5 無 電感繞組數 1 2 4 6 4 表2 本發明與參考文獻之比較表 4. Comparison of inductor windings: The converter (1) of the present invention and the reference [2] have a lower voltage gain than the converter of the reference [3], mainly because the number of coupled inductor windings is less than 2 sets. high boost converter traditional boost converter Literature [1] Literature [2] Literature [3] this invention Voltage conversion ratio
Figure 02_image124
Figure 02_image126
Figure 02_image128
Figure 02_image130
Figure 02_image132
 The switching stress is represented by n=1
Figure 02_image134
Figure 02_image134
Figure 02_image135
Figure 02_image137
Figure 02_image139
 Number of clearances 1 2 2 2 2 Number of Diodes 1 1 4 8 4 On-ratio limit none none D>0.5 D>0.5 none Number of inductor windings 1 2 4 6 4 Table 2 Comparison table between the present invention and references

因此，在元件數量差不多的條件下，本發明之該轉換器(1)具有高電壓轉換比之最佳應用價值。Therefore, under the condition that the number of components is similar, the converter (1) of the present invention has the best application value of high voltage conversion ratio.

參考文獻：references:

［1］L. S. Yang, T. J. Liang, and J. F. Chen, “Transformerless DC-DC converter with high step-up voltage gain,” IEEE Trans. Industrial Electronics, Vol. 56, No. 8, pp. 3144-3152, 2009. [1] LS Yang, TJ Liang, and JF Chen, “Transformerless DC-DC converter with high step-up voltage gain,” IEEE Trans. Industrial Electronics , Vol. 56, No. 8, pp. 3144-3152, 2009.

［2］K. C. Tseng and C. C. Huang, “High Step-Up High-Efficiency Interleaved Converter with Voltage Multiplier Module for Renewable Energy System,” IEEE Transactions on Power Electronics, Vol. 61, No. 3, pp. 1311-1319, March 2014. [2] KC Tseng and CC Huang, “High Step-Up High-Efficiency Interleaved Converter with Voltage Multiplier Module for Renewable Energy System,” IEEE Transactions on Power Electronics , Vol. 61, No. 3, pp. 1311-1319, March 2014.

［3］李欣達，具繞組交越耦合電感之嶄新交錯式高升壓DC-DC轉換器研製，碩士論文，崑山科技大學電機工程系，2017。[3] Li Xinda, Development of a New Interleaved High Boost DC-DC Converter with Winding Cross-Coupling Inductance, Master's Thesis, Department of Electrical Engineering, Kunshan University of Science and Technology, 2017.

藉由以上所述，本發明之使用實施說明可知，本發明與現有技術手段相較之下，本發明主要係具有下列優點：From the above, the use and implementation description of the present invention shows that compared with the prior art means, the present invention mainly has the following advantages:

1.簡單創新電路：轉換器電路對稱不複雜且元件少，利用切換式耦合電感技術，同時達到切換式電感及電壓倍增模組的功用，使轉換器達到高升壓之特性。1. Simple and innovative circuit: The converter circuit is not symmetrical and has few components. Using the switch-type coupled inductor technology, it achieves the functions of the switch-type inductor and the voltage multiplier module at the same time, so that the converter can achieve the characteristics of high boost.

2.較高升壓增益：不操作在極端寬大的導通責任比下，轉換器亦能具有高升壓的電壓轉換比，且可利用匝數比進一步提高轉換器之電壓增益。2. Higher boost gain: The converter can also have a high boost voltage conversion ratio without operating at an extremely wide turn-on duty ratio, and the turns ratio can be used to further increase the voltage gain of the converter.

3.較高功率應用：在不增加元件耐壓、耐流下，使轉換器可以處理更大的功率，最大輸出功率為1 kW。3. Higher power application: The converter can handle higher power without increasing the voltage and current resistance of the components, and the maximum output power is 1 kW.

4.較低電壓應力：在同樣功率的應用下，因轉換器之對稱架構，以分壓方式負擔一半的高輸出電壓，故可降低開關元件上的電壓應力。4. Lower voltage stress: Under the same power application, due to the symmetrical structure of the converter, half of the high output voltage is borne by the voltage division method, so the voltage stress on the switching element can be reduced.

5.高的轉換效率：因開關具有低電壓應力，故可用較低額定耐壓之開關，能降低導通電阻，使效率提升，亦可降低開關的成本，且交錯操作及對稱架構使電流均流分擔，在相同導通比下，除了可達成其他轉換器無法達到的高電壓增益，預期最高效率，可達92 %以上。5. High conversion efficiency: Because the switch has low voltage stress, a switch with a lower rated withstand voltage can be used, which can reduce the on-resistance, improve the efficiency, and also reduce the cost of the switch, and the interleaved operation and symmetrical structure allow the current to flow. Under the same conduction ratio, in addition to the high voltage gain that other converters cannot achieve, the expected maximum efficiency can reach more than 92%.

然而前述之實施例或圖式並非限定本發明之產品結構或使用方式，任何所屬技術領域中具有通常知識者之適當變化或修飾，皆應視為不脫離本發明之專利範疇。However, the foregoing embodiments or drawings do not limit the product structure or usage of the present invention, and any appropriate changes or modifications made by those with ordinary knowledge in the technical field should be regarded as not departing from the scope of the present invention.

綜上所述，本發明實施例確能達到所預期之使用功效，又其所揭露之具體構造，不僅未曾見諸於同類產品中，亦未曾公開於申請前，誠已完全符合專利法之規定與要求，爰依法提出發明專利之申請，懇請惠予審查，並賜准專利，則實感德便。To sum up, the embodiment of the present invention can indeed achieve the expected use effect, and the specific structure disclosed is not only not seen in similar products, but also has not been disclosed before the application, which fully complies with the provisions of the patent law In accordance with the requirements, I would like to file an application for an invention patent in accordance with the law, and I sincerely request that it be reviewed and granted the patent.

1:轉換器1: Converter

Figure 02_image001
:輸入電壓
Figure 02_image001
:Input voltage

Figure 02_image003
:第一電容
Figure 02_image003
: first capacitor

Figure 02_image005
:第二電容
Figure 02_image005
: second capacitor

Figure 02_image007
:第三電容
Figure 02_image007
: The third capacitor

Figure 02_image009
:第四電容
Figure 02_image009
: Fourth capacitor

Figure 02_image011
:第五電容
Figure 02_image011
: Fifth capacitor

Figure 02_image013
:第六電容
Figure 02_image013
: sixth capacitor

Figure 02_image015
:第一功率開關
Figure 02_image015
: first power switch

Figure 02_image017
:第二功率開關
Figure 02_image017
: Second power switch

Figure 02_image019
:第一耦合電感一次側
Figure 02_image019
: Primary side of the first coupled inductor

Figure 02_image021
:第一耦合電感二次側
Figure 02_image021
: Secondary side of the first coupled inductor

Figure 02_image023
:第一磁化電感
Figure 02_image023
: first magnetizing inductance

Figure 02_image025
:第二耦合電感一次側
Figure 02_image025
: Primary side of the second coupled inductor

Figure 02_image027
:第二耦合電感二次側
Figure 02_image027
: Secondary side of the second coupled inductor

Figure 02_image029
:第二磁化電感
Figure 02_image029
: Second magnetizing inductance

Figure 02_image031
:漏電感
Figure 02_image031
: leakage inductance

Figure 02_image033
:第一二極體
Figure 02_image033
: first diode

Figure 02_image035
:第二二極體
Figure 02_image035
: second diode

Figure 02_image037
:第三二極體
Figure 02_image037
: third diode

Figure 02_image039
:第四二極體
Figure 02_image039
: Fourth diode

Figure 02_image041
:負載
Figure 02_image041
:load

第一圖：本發明之電路圖The first picture: the circuit diagram of the present invention

第二圖：本發明之時序圖所The second figure: the timing diagram of the present invention

第三圖：本發明之預備階段等效線性電路圖Figure 3: Equivalent linear circuit diagram in the preliminary stage of the present invention

第四圖：本發明之第一階段等效線性電路圖Figure 4: Equivalent linear circuit diagram of the first stage of the present invention

第五圖：本發明之第二階段等效線性電路圖Figure 5: Equivalent linear circuit diagram of the second stage of the present invention

第六圖：本發明之第三階段等效線性電路圖Figure 6: Equivalent linear circuit diagram of the third stage of the present invention

第七圖：本發明之第四階段等效線性電路圖Figure 7: Equivalent linear circuit diagram of the fourth stage of the present invention

第八圖：本發明之模擬電路示意圖Figure 8: Schematic diagram of the analog circuit of the present invention

第九圖：本發明之開關驅動信號

Figure 02_image043
、
Figure 02_image045
與輸入電壓
Figure 02_image047
及輸出電壓
Figure 02_image049
的模擬波形圖［交錯式切換操作］ Figure 9: The switch driving signal of the present invention
Figure 02_image043
,
Figure 02_image045
with input voltage
Figure 02_image047
and output voltage
Figure 02_image049
Analog waveform diagram of [Interleaved switching operation]

第十圖：本發明之開關驅動信號

Figure 02_image043
、
Figure 02_image045
與輸入電壓
Figure 02_image047
及輸出電壓
Figure 02_image049
的模擬波形圖［同步式切換操作］ Figure 10: Switch driving signal of the present invention
Figure 02_image043
,
Figure 02_image045
with input voltage
Figure 02_image047
and output voltage
Figure 02_image049
[Synchronous switching operation]

第十一圖：本發明於匝數比n=1時之電壓轉換比比較曲線圖The eleventh figure: the comparison curve of the voltage conversion ratio of the present invention when the turns ratio n=1

第十二圖：本發明於匝數比n=3時之電壓轉換比比較曲線圖The twelfth figure: the comparison curve of the voltage conversion ratio of the present invention when the turns ratio n=3

1:轉換器 1: Converter

V in:輸入電壓 V in : input voltage

C 1:第一電容 C 1 : the first capacitor

C 2:第二電容 C 2 : second capacitor

C 3:第三電容 C 3 : the third capacitor

C 4:第四電容 C 4 : Fourth capacitor

C 5:第五電容 C 5 : Fifth capacitor

C 6:第六電容 C 6 : sixth capacitor

S 1:第一功率開關 S 1 : the first power switch

S 2:第二功率開關 S 2 : Second power switch

N p1:第一耦合電感一次側 N p 1 : the primary side of the first coupled inductor

N p2:第一耦合電感二次側 N p 2 : the secondary side of the first coupled inductor

L m1:第一磁化電感 L m 1 : the first magnetizing inductance

N s1:第二耦合電感一次側 N s 1 : the primary side of the second coupled inductor

N s2:第二耦合電感二次側 N s 2 : the secondary side of the second coupled inductor

L m2:第二磁化電感 L m 2 : second magnetizing inductance

L s :漏電感 L s : leakage inductance

D 1:第一二極體 D 1 : first diode

D 2:第二二極體 D 2 : Second diode

D 3:第三二極體 D 3 : the third diode

D 4:第四二極體 D 4 : Fourth diode

R o :負載 R o : load

Claims (5)

一種對稱切換型高升壓直流轉換器，其主要係令轉換器於輸入電壓之正極分別連接第一電容之正極、第一功率開關之第一端及第一耦合電感一次側之第一端，該輸入電壓之負極分別連接第二電容之負極、第二功率開關之第二端及第二耦合電感一次側之第一端，該第一電容之負極分別連接該第二電容之正極、第三電容之負極及第四電容之正極，該第一功率開關之第二端分別連接該第二耦合電感一次側之第二端及第四二極體之負極，該第一耦合電感一次側之第二端分別連接該第二功率開關之第一端及第三二極體之正極，該第三二極體之負極分別連接該第三電容之正極、第六電容之負極及第二二極體之正極，該第六電容之正極分別連接第五電容之負極及第二耦合電感二次側之第二端，該第二二極體之負極分別連接第一耦合電感二次側之第二端及第一二極體之正極，該第一耦合電感二次側之第一端與該第二耦合電感二次側之第一端相連接，該第一二極體之負極分別連接該第五電容之正極及負載之第一端，該負載之第二端則分別連接該第四電容之負極及該第四二極體之正極。 A symmetric switching type high-boost DC converter is mainly used to connect the positive pole of the input voltage to the positive pole of the first capacitor, the first end of the first power switch and the first end of the primary side of the first coupling inductor, respectively, The negative pole of the input voltage is respectively connected to the negative pole of the second capacitor, the second terminal of the second power switch and the first terminal of the primary side of the second coupling inductor, the negative pole of the first capacitor is respectively connected to the positive pole of the second capacitor, the third terminal The negative electrode of the capacitor and the positive electrode of the fourth capacitor, the second end of the first power switch is respectively connected to the second end of the primary side of the second coupling inductor and the negative electrode of the fourth diode, and the second end of the primary side of the first coupling inductor is connected. The two terminals are respectively connected to the first terminal of the second power switch and the positive pole of the third diode, and the negative pole of the third diode is respectively connected to the positive pole of the third capacitor, the negative pole of the sixth capacitor and the second diode The positive electrode of the sixth capacitor is connected to the negative electrode of the fifth capacitor and the second end of the secondary side of the second coupling inductor respectively, and the negative electrode of the second diode is respectively connected to the second end of the secondary side of the first coupling inductor and the positive pole of the first diode, the first end of the secondary side of the first coupled inductor is connected to the first end of the secondary side of the second coupled inductor, and the negative pole of the first diode is connected to the fifth The positive electrode of the capacitor and the first end of the load, and the second end of the load are respectively connected to the negative electrode of the fourth capacitor and the positive electrode of the fourth diode. 如請求項1所述對稱切換型高升壓直流轉換器，其中，該轉換器於該第一耦合電感一次側形成有第一磁化電感。 The symmetric switching type high-boost DC converter according to claim 1, wherein the converter has a first magnetizing inductance formed on the primary side of the first coupling inductance. 如請求項1所述對稱切換型高升壓直流轉換器，其中，該轉 換器於該第二耦合電感一次側形成有第二磁化電感。 The symmetric switching type high boost DC converter according to claim 1, wherein the converter The converter forms a second magnetizing inductance on the primary side of the second coupled inductance. 如請求項1所述對稱切換型高升壓直流轉換器，其中，該轉換器於於該第六電容之正極與該第二耦合電感二次側之第二端之間形成有漏電感。 The symmetric switching type high boost DC converter as claimed in claim 1, wherein the converter has a leakage inductance formed between the anode of the sixth capacitor and the second end of the secondary side of the second coupling inductor. 如請求項1所述對稱切換型高升壓直流轉換器，其中，該轉換器之電壓轉換比係為
Figure 110121010-A0305-02-0021-1
，其中D為導通比。 The symmetric switching type high boost DC converter according to claim 1, wherein the voltage conversion ratio of the converter is:
Figure 110121010-A0305-02-0021-1
, where D is the conduction ratio.
TW110121010A 2021-06-09 2021-06-09 Symmetrical switching type high boost dc converter TWI765740B (en)

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