TWI578684B - Asymmetric half-bridge high step-down converter - Google Patents
Asymmetric half-bridge high step-down converter Download PDFInfo
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本發明係有關於一種非對稱半橋高降壓轉換器,尤其是指一種具有高降壓比、高轉換效率及低電壓應力等功效,而在其整體施行使用上更增實用功效特性之非對稱半橋高降壓轉換器創新設計者。 The invention relates to an asymmetric half-bridge high buck converter, in particular to a function of high step-down ratio, high conversion efficiency and low voltage stress, and more practical utility characteristics in its overall implementation. Innovative designer of symmetrical half-bridge high buck converters.
按,由於油源日趨減少,使得節能意識高漲,由美國環境保護組織(The U.S.Environmental Protection Agency)和美國能源部門(The U.S.Department of Energy)共同發起的Energy Star標籤認證計劃成立於1992年,其目的是讓消費者透過電子或電器產品上的能源標籤來識別具節能效益的產品,進而減低溫室效應。而Energy Star 4.0將80 PLUS規範列入標準,對提供給個人電腦內部的AC-DC切換式電源供應器,無論在電腦處在待機或是休眠狀態時,電 源供應器在輸出負載20%、50%、100%時,最少要有80%以上的效率。此外,能源之星也與Intel發起的CSCI拯救氣候行動計劃(Climate Savers Computing Initiative,CSCI)合作,加快節能技術和規範的採用。由於80 PLUS符合節能與環保的思潮,因此目前新推出的電源供應器幾乎都以支援80 PLUS規範為主要賣點,以節能省電的特色,來獲得歐美消費市場認同。在2008年80 PLUS規範增加了更嚴格的銅、銀、金牌標章認證。而且2009年7月1日起Energy Star 5.0和80 PLUS銅牌標章兩者有同樣的效率要求。因此選擇使用符合80 PLUS和Energy Star認可的電源供應器,將有助於節省更多的能源及成本。因此設計高效率之電源轉換器,滿足日趨嚴苛的電源規範已是時勢所趨。 According to the decreasing oil source, the awareness of energy conservation is high. The Energy Star label certification program jointly sponsored by The US Environmental Protection Agency and The USDepartment of Energy was established in 1992. The goal is to enable consumers to identify energy-efficient products through energy labels on electronic or electrical products, thereby reducing the greenhouse effect. Energy Star 4.0 puts the 80 PLUS specification in the standard, for the AC-DC switched power supply provided to the PC, whether the computer is in standby or hibernation, The source supply must have a minimum efficiency of 80% or more at the output load of 20%, 50%, and 100%. In addition, ENERGY STAR has partnered with Intel's CSCI Climate Savers Computing Initiative (CSCI) to accelerate the adoption of energy-efficient technologies and specifications. Because 80 PLUS meets the trend of energy saving and environmental protection, the newly launched power supply is almost always supporting the 80 PLUS specification as the main selling point, and it is recognized by the European and American consumer market with the characteristics of energy saving and power saving. In 2008, the 80 PLUS specification added stricter copper, silver, and gold medal certification. And on July 1, 2009, Energy Star 5.0 and 80 PLUS bronze medals have the same efficiency requirements. Therefore, choosing to use 80 PLUS and Energy Star approved power supplies will help save more energy and cost. Therefore, designing high-efficiency power converters to meet increasingly stringent power supply specifications is a constant trend.
其中,就一般常見之轉換器而言,請參閱第二十一圖現有之降壓式轉換器電路圖所示,該降壓式轉換器(2)主要係透過開關S與二極體D組成的斬波器得到脈波電壓後,經過由電感L及電容C所組成之二階低通濾波器取出輸出電壓V O ,其滿足V O =DV in ,其透過開關s導通責任比D調整;然而,該降壓式轉換器(2)應用於高輸入電壓低輸出電壓時,操作之導通責任比需極端窄小,易受雜訊干擾,且不易做閉迴路穩壓控制,又開關S利用率低,影響電路效率,同時該開關S屬硬性切換,無柔性切換性能,在高頻切換時,切換損失會導致開關S元件溫度上升,減少開關S元件壽命。 For the general converter, please refer to the circuit diagram of the existing buck converter of the twenty-first figure. The buck converter (2) mainly consists of the switch S and the diode D. After the chopper obtains the pulse voltage, the output voltage V O is taken through a second-order low-pass filter composed of the inductor L and the capacitor C , which satisfies V O = DV in , and the conduction ratio D is adjusted through the switch s ; however, When the buck converter (2) is applied to a high input voltage and low output voltage, the operational conduction duty ratio is extremely narrow, susceptible to noise interference, and it is difficult to perform closed loop voltage regulation control, and the switch S utilization rate is low. It affects the efficiency of the circuit. At the same time, the switch S is hardly switched and has no flexible switching performance. When switching at high frequency, the switching loss will cause the temperature of the switch S component to rise and reduce the life of the switch S component.
請再參閱第二十二圖現有之雙晶順向式轉換器電路圖所示,該雙晶順向式轉換器(3)主要係加入變壓器以達到電氣隔離,輸出電壓V O =DV in /n,雖有D<0.5的限制,但是具有降壓彈性,不需利用極小的導通責任比達成高降壓特性,而是利用變壓器匝比n>1達成,如此,開關導通責任比即可操作在正常可控制範圍,此外,該雙晶順向式轉換器(3)的兩個主開關S 1、S 2均會被二極體箝位在輸入電壓V in ,因此適合應用於大輸入電壓場合;然而,該雙晶順向式轉換器(3)於使用上卻發現,由於其D<0.5的限制,限縮該雙晶順向式轉換器(3)輸入電壓的應用範圍,且若要達到高降壓則變壓器的匝比n要越大,導致變壓器的體積變大,會產生寄生電容、繞線電組及漏電感也會增大,使整體電路的突波上升,造成元件需承受更大的應力,亦使該雙晶順向式轉換器(3)效率下降,應用於高輸入電壓低輸出電壓時,變壓器的二次側之整流二極體與磁性元件,仍須承受大電流應力,會導致元件損失上升,同時其開關屬硬性切換,無柔性切換性能,在高頻切換時,切換損失會導致開關元件溫度上升,減少開關元件壽命。 Referring to the circuit diagram of the existing bimorphic forward converter of the twenty-second figure, the bimorphic forward converter (3) is mainly added to the transformer to achieve electrical isolation, and the output voltage V O = DV in / n Although there is a limit of D <0.5, it has a bucking flexibility, and does not need to achieve a high step-down characteristic with a small conduction responsibility ratio, but uses a transformer 匝 ratio n > 1, so that the switch conduction duty ratio can be operated. Normally controllable range, in addition, the two main switches S 1 and S 2 of the dual crystal forward converter (3) are clamped to the input voltage V in by the diode, so it is suitable for large input voltage applications. However, the dual-crystal forward converter (3) is found to have a limit of the application range of the input voltage of the bimorphic forward converter (3) due to its limitation of D <0.5, and if to achieve a high step-down transformer, the turns ratio of the larger to n, causing the volume of the transformer increases, a parasitic capacitance is generated, the electric wire groups and the leakage inductance will increase the overall circuit surge increase, resulting in the need to withstand element The greater stress also reduces the efficiency of the twin-crystal forward converter (3). When applied to high input voltage and low output voltage, the rectifying diode and magnetic component on the secondary side of the transformer still have to withstand large current stress, which will lead to component loss rise. At the same time, the switch is hard switching and has no flexible switching performance. When the high frequency is switched, the switching loss causes the temperature of the switching element to rise, reducing the life of the switching element.
另,請再參閱第二十三圖現有之雙晶順向式高降壓轉換器電路圖所示,該雙晶順向式高降壓轉換器(4)為改善變壓器匝比n過大,又需要達到高降壓目的,在整流二極體D 1後串聯降壓電感〔buck inductor〕,使i LB =i L 時變壓器能量才會傳至輸出側,使二次側實際導通責任比小於開關導通責任比D,而達到高降壓目的;然而,該雙晶順向式高降壓轉換器(4)於使用上卻 發現,由於其D<0.5的限制,限縮該雙晶順向式高降壓轉換器(4)輸入電壓的應用範圍,應用於高輸入電壓低輸出電壓時,變壓器的二次側二極體與磁性元件,須承受大電流應力,導致元件損失與熱應力上升,並由於該雙晶順向式高降壓轉換器(4)之電壓轉換比受到降壓電感影響,且與頻率有關,使得小信號建模時須將頻率當做一個變數,不僅增加小信號模式推導的難度,也使穩壓控制較難達成,同時其開關屬硬性切換,無柔性切換性能,在高頻切換時,切換損失會導致開關元件溫度上升,減少開關元件壽命。 In addition, please refer to the circuit diagram of the existing bimorph forward high-voltage buck converter shown in the twenty-third figure. The dual-crystal forward high-voltage buck converter (4) needs to improve the transformer turns ratio n and needs To achieve high buck, the buck inductor is connected in series after rectifying diode D 1 so that the transformer energy is transmitted to the output side when i LB = i L , so that the secondary conduction actual duty ratio is smaller than the switch conduction. Responsibility ratio D , and achieve high buck purpose; however, the twin-crystal forward high-voltage buck converter (4) found in use, due to its limit of D <0.5, the shrinkage of the twin-crystal forward high Buck converter (4) application range of input voltage, when applied to high input voltage and low output voltage, the secondary side diode and magnetic component of the transformer must withstand large current stress, resulting in component loss and thermal stress rise, and Since the voltage conversion ratio of the bi-directional forward high-voltage buck converter (4) is affected by the step-down inductance and is related to the frequency, the frequency must be regarded as a variable in small signal modeling, which not only increases the derivation of the small signal mode. Difficulty also makes the voltage control difficult to achieve, while Switch genus hard handover, no soft switching performance at high frequency switching, the switching loss of the switching element temperature rise will lead to reduced life of the switching element.
又,請再參閱第二十四圖現有之非對稱半橋式轉換器電路圖所示,該非對稱半橋式轉換器(5)利用主開關與輔助開關進行互補操作時,讓兩個驅動信號產生死帶,在此時間區間內,使開關的寄生電容與變壓器的漏電感產生共振迴路,經共振使開關跨壓下降至零之後,開關在切換為on,達到零電壓柔性切換;然而,該非對稱半橋式轉換器(5)於使用過程中,若要達到高降壓則變壓器的匝比n要越大,導致變壓器的體積變大,會產生寄生電容、繞線電組及漏電感也會增大,使整體電路的突波上升,造成元件需承受更大的應力,亦使轉換器效率下降。二次側半導體元件與磁性元件須承受大電流應力,導致元件損失上升,且於高降壓成輸出低壓大電流及高功率應用時,二次側二極體與磁性元件,須承受大電流應力,導致元件損失與熱應力上升,並因開關驅動信號須互補且需具有死帶,於整體電路設計上較為複雜。 In addition, please refer to the circuit diagram of the existing asymmetric half-bridge converter of the twenty-fourth figure. The asymmetric half-bridge converter (5) uses the main switch and the auxiliary switch to perform complementary operations, so that two driving signals are generated. In this time interval, the parasitic capacitance of the switch and the leakage inductance of the transformer generate a resonant circuit. After the resonance crosses the voltage to zero, the switch switches to on to achieve zero voltage flexible switching; however, the asymmetry half-bridge converter (5) in use, to achieve a high step-down transformer, the turns ratio of the larger to n, causing the volume of the transformer increases, a parasitic capacitance is generated, the electric wire groups and the leakage inductance will The increase causes the surge of the overall circuit to rise, causing the component to withstand greater stress and also degrading the efficiency of the converter. The secondary side semiconductor component and the magnetic component are subjected to large current stress, resulting in an increase in component loss, and the secondary side diode and the magnetic component are subjected to a large current stress when the high voltage is reduced to output low voltage, high current, and high power application. As a result, component loss and thermal stress rise, and the switch drive signal must be complementary and need to have a dead band, which is complicated in the overall circuit design.
緣是,發明人有鑑於此,秉持多年該相關行業之豐富設計開發及實際製作經驗,針對現有之結構及缺失再予以研究改良,提供一種非對稱半橋高降壓轉換器,以期達到更佳實用價值性之目的者。 In view of this, the inventors have provided a kind of asymmetric half-bridge high-buck converter for better performance based on years of rich experience in design, development and actual production of related industries, and research and improvement on existing structures and defects. The purpose of practical value.
本發明之主要目的在於提供一種非對稱半橋高降壓轉換器,其主要係具有高降壓比、高轉換效率及低電壓應力等功效,而在其整體施行使用上更增實用功效特性者。 The main object of the present invention is to provide an asymmetric half-bridge high buck converter, which mainly has the functions of high step-down ratio, high conversion efficiency and low voltage stress, and has more practical utility characteristics in its overall implementation. .
本發明非對稱半橋高降壓轉換器之主要目的與功效,係由以下具體技術手段所達成: The main purpose and effect of the asymmetric half-bridge high buck converter of the present invention are achieved by the following specific technical means:
其主要係令轉換器於輸入電源V in 之正極並聯有輔助開關S 2的第一端及電容C B 的第一端,於輸入電源V in 之負極則連接有主開關S 1的第一端,該主開關S 1的第二端則並聯有輔助開關S 2的第二端及電感L r 的第一端,該電容C B 的第二端與該電感L r 的第二端則連接有變壓器的一次側,於該變壓器的二次側正極連接有整流二極體D 1的正極,該整流二極體D 1的負極連接有降壓電感L b 的第一端,該降壓電感L b 的第二端並聯有飛輪二極體D 2的負極及輸出電感L o 的第一端,該輸出電感L o 的第二端並聯有輸出電容C o 的第一端及負載R的第一端,於該變壓器的二次側負極連接有該飛輪二極體D 2的正極、輸出電容C o 的第二端及負載R的第二端。 The main purpose is that the converter is connected to the first end of the auxiliary switch S 2 and the first end of the capacitor C B in parallel with the anode of the input power source V in , and the first end of the main switch S 1 is connected to the cathode of the input power source V in The second end of the main switch S 1 is connected in parallel with the second end of the auxiliary switch S 2 and the first end of the inductor L r , and the second end of the capacitor C B is connected to the second end of the inductor L r the primary side of the transformer, the secondary side of the transformer is connected to the positive electrode of the positive rectifier diode D 1, the rectifying diode D 1 is connected to the negative terminal of a first buck inductor L B of the buck inductor L b of the second end parallel with a flywheel diode D of the first end of the output inductor L o and the negative electrode 2, a second end of the output inductor L o connected in parallel with a first output of a first end of capacitor C o and load R, The anode of the flywheel diode D 2 , the second end of the output capacitor C o and the second end of the load R are connected to the secondary side of the transformer.
(1)‧‧‧轉換器 (1)‧‧‧ converter
(11)‧‧‧變壓器 (11)‧‧‧Transformers
(2)‧‧‧降壓式轉換器 (2) ‧‧‧ buck converter
(3)‧‧‧雙晶順向式轉換器 (3)‧‧‧Double-crystal forward converter
(4)‧‧‧雙晶順向式高降壓轉換器 (4)‧‧‧Double-Phase Forward High-Buck Converter
(5)‧‧‧非對稱半橋式轉換器 (5) ‧‧‧Asymmetric Half-Bridge Converter
第一圖:本發明之電路圖 First picture: circuit diagram of the invention
第二圖:本發明之主要元件時序波形圖 Second picture: timing waveform diagram of the main components of the present invention
第三圖:本發明之第一操作階段等效電路圖 Third figure: equivalent circuit diagram of the first operation stage of the present invention
第四圖:本發明之第二操作階段等效電路圖 Fourth figure: equivalent circuit diagram of the second operation stage of the present invention
第五圖:本發明之第三操作階段等效電路圖 Figure 5: Equivalent circuit diagram of the third operation stage of the present invention
第六圖:本發明之第四操作階段等效電路圖 Figure 6: Equivalent circuit diagram of the fourth operation stage of the present invention
第七圖:本發明之第五操作階段等效電路圖 Figure 7: Equivalent circuit diagram of the fifth operation stage of the present invention
第八圖:本發明之第六操作階段等效電路圖 Figure 8: Equivalent circuit diagram of the sixth operation stage of the present invention
第九圖:本發明之第七操作階段等效電路圖 Ninth diagram: equivalent circuit diagram of the seventh operation stage of the present invention
第十圖:本發明之第八操作階段等效電路圖 Figure 11: Equivalent circuit diagram of the eighth operation stage of the present invention
第十一圖:本發明之第九操作階段等效電路圖 Eleventh drawing: equivalent circuit diagram of the ninth operation stage of the present invention
第十二圖:本發明之第十操作階段等效電路圖 Twelfth figure: equivalent circuit diagram of the tenth operation stage of the present invention
第十三圖:本發明之主開關驅動信號、輸入電源及輸出電壓的模擬波形圖 Figure 13: Analog waveform diagram of the main switch drive signal, input power supply and output voltage of the present invention
第十四圖:本發明之主開關驅動信號、輸入電源及輸出電壓的實作波形圖 Figure 14: Actual waveform diagram of the main switch drive signal, input power supply and output voltage of the present invention
第十五圖:本發明之主開關驅動信號與其跨壓模擬波形圖 The fifteenth figure: the main switch driving signal and the cross-voltage analog waveform diagram of the invention
第十六圖:本發明之主開關驅動信號與其跨壓實作波形圖 Figure 16: The main switch driving signal of the present invention and its cross-voltage implementation waveform
第十七圖:本發明之輔助開關驅動信號與其跨壓模擬波形圖 Figure 17: The auxiliary switch drive signal and its cross-over voltage analog waveform diagram of the present invention
第十八圖:本發明之輔助開關驅動信號與其跨壓實作波形圖 Figure 18: Waveform diagram of the auxiliary switch drive signal and its cross-voltage implementation of the present invention
第十九圖:本發明之降壓電感電流與輸出電感電流模擬波形圖 Figure 19: Analog waveform diagram of the step-down inductor current and output inductor current of the present invention
第二十圖:本發明之降壓電感電流與輸出電感電流實作波形圖 Figure 20: The waveform diagram of the step-down inductor current and output inductor current of the present invention
第二十一圖:現有之降壓式轉換器電路圖 Figure 21: Existing buck converter circuit diagram
第二十二圖:現有之雙晶順向式轉換器電路圖 Figure 22: Existing dual crystal forward converter circuit diagram
第二十三圖:現有之雙晶順向式高降壓轉換器電路圖 Twenty-third picture: existing dual crystal forward high buck converter circuit diagram
第二十四圖:現有之非對稱半橋式轉換器電路圖 Figure 24: Existing asymmetric half-bridge converter circuit diagram
為令本發明所運用之技術內容、發明目的及其達成之功效有更完整且清楚的揭露,茲於下詳細說明之,並請一併參閱所揭之圖式及圖號: For a more complete and clear disclosure of the technical content, the purpose of the invention and the effects thereof achieved by the present invention, it is explained in detail below, and please refer to the drawings and drawings:
首先,請參閱第一圖本發明之電路圖所示,本發明之轉換器(1)主要係於輸入電源V in 之正極並聯有輔助開關S 2的第一端及電容C B 的第一端,於輸入電源V in 之負極則連接有主開關S 1的第一端,該主開關S 1的第二端則並聯有輔助開關S 2的第二端及電感L r 的第一端,該電容C B 的第二端與該電感L r 的第二端則連接有變 壓器(11)的一次側,於該變壓器(11)的二次側正極連接有整流二極體D 1的正極,該整流二極體D 1的負極連接有降壓電感L b 的第一端,該降壓電感L b 的第二端並聯有飛輪二極體D 2的負極及輸出電感L o 的第一端,該輸出電感L o 的第二端並聯有輸出電容C o 的第一端及負載R的第一端,於該變壓器(11)的二次側負極連接有該飛輪二極體D 2的正極、輸出電容C o 的第二端及負載R的第二端。 First, referring to the first diagram of the circuit diagram of the present invention, the converter (1) of the present invention is mainly connected to the first end of the auxiliary switch S 2 and the first end of the capacitor C B in parallel with the positive pole of the input power source V in V in the input power of the negative electrode is connected to a first terminal of the primary switch S 1, the second main terminal of the switch S 1 is connected in parallel a first end and a second end of the inductor L r auxiliary switch S 2, and the capacitance The second end of C B and the second end of the inductor L r are connected to the primary side of the transformer (11), and the positive pole of the rectifier diode (11) is connected to the positive pole of the rectifying diode D 1 , the rectification diode D 1 is connected to the negative terminal of a first buck inductor L b and the second end of the buck inductor L b connected in parallel with a first end of the flywheel diode D and the negative output inductor L o 2, the The second end of the output inductor L o is connected in parallel with the first end of the output capacitor C o and the first end of the load R , and the anode of the flywheel diode D 2 is connected to the negative side of the secondary side of the transformer (11) The second end of the capacitor C o and the second end of the load R.
而該轉換器(1)在使用過程中,根據該主開關S 1、該輔助開關S 2、該主開關S 1的本體二極體D S1、該輔助開關S 2的本體二極體D S2、該整流二極體D 1、該飛輪二極體D 2之導通與否,可以將該轉換器(1)在一個切換週期T s 的動作,分成十個線性階段,其各線性階段線性等效電路以及主要元件波形如下所示,請再一併參閱第二圖本發明之主要元件時序波形圖所示: And the converter (1) during use, in accordance with the primary switch S 1, the auxiliary switch S 2, the primary switch S of the body 1 of the diode D S 1, the auxiliary switch S of the body 2 of the diode D S 2 , the rectifying diode D 1 , and the flywheel diode D 2 are turned on or off, and the converter (1) can be divided into ten linear stages in a switching period T s , and each linear phase thereof The linear equivalent circuit and the main component waveforms are shown below. Please refer to the second diagram of the main component timing waveform diagram of the present invention as shown in the following figure:
第一階段〔t 0~t 1〕:〔主開關S 1:off、輔助開關S 2:off、主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:off、整流二極體D 1:on、飛輪二極體D 2:off〕:請再一併參閱第三圖本發明之第一操作階段等效電路圖所示,本階段當主開關S 1切換為off時,主開關S 1跨壓v ds1線性上升,輔助開關S 2跨壓v ds2線性下降,當該變壓器(11)二次側之飛輪二極體D 2切換為on時進入下一階段。 The first stage [ t 0 ~ t 1 ]: [main switch S 1 :off, auxiliary switch S 2 :off, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :off, rectifying diode D 1 :on, flywheel diode D 2 :off]: Please refer to the third figure again. The equivalent circuit diagram of the first operation stage of the present invention is shown at this stage. when switch S 1 is switched to off, the voltage across the main switch S 1 is v ds 1 increases linearly, the voltage across the auxiliary switch S 2 v ds 2 decreases linearly when the flywheel (11) of the secondary side of the transformer switching diode D 2 is On the next stage.
第二階段〔t 1~t 2〕:〔主開關S 1:off、輔助開關S 2:off、 主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:off、整流二極體D 1:on、飛輪二極體D 2:on〕:請再一併參閱第四圖本發明之第二操作階段等效電路圖所示,本階段當飛輪二極體D 2切換為on時,該變壓器(11)二次側之二極體電流開始換向,主開關S 1跨壓v ds1共振上升,輔助開關S 2跨壓v ds2共振下降,當輔助開關S 2跨壓v ds2共振下降至零後,該輔助開關S 2的本體二極體D S2切換為on時進入下一階段。 Second stage [ t 1 ~ t 2 ]: [main switch S 1 :off, auxiliary switch S 2 :off, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :off, rectifying diode D 1 :on, flywheel diode D 2 :on]: Please refer to the fourth diagram of the second operational stage of the present invention as shown in the equivalent circuit diagram, this stage is as the flywheel When the diode D 2 is switched to on, the diode current on the secondary side of the transformer (11) starts to commutate, the main switch S 1 rises in resonance across the voltage v ds 1 , and the auxiliary switch S 2 rises in resonance across the voltage v ds 2 . When the auxiliary switch S 2 is cooled down to zero across the voltage v ds 2 , the body diode D S 2 of the auxiliary switch S 2 is switched to on to proceed to the next stage.
第三階段〔t 2~t 3〕:〔主開關S 1:off、輔助開關S 2:off、主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:on、整流二極體D 1:on、飛輪二極體D 2:on〕:請再一併參閱第五圖本發明之第三操作階段等效電路圖所示,本階段當輔助開關S 2跨壓v ds2共振下降至零,輔助開關S 2的本體二極體D S2切換為on,輔助開關S 2隨時可以切換為on達到ZVS,當輔助開關S 2切換為on時進入下一階段。 The third stage [ t 2 ~ t 3 ]: [main switch S 1 :off, auxiliary switch S 2 :off, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :on, rectifying diode D 1 :on, flywheel diode D 2 :on]: Please refer to the fifth diagram for the third stage of operation of the present invention as shown in the equivalent circuit diagram. switch S 2 cross voltage V DS 2 resonance drops to zero, the auxiliary switch S of the body 2 of the diode D S 2 is switched on, the auxiliary switch S 2 ready to be switched on to achieve the ZVS, when an auxiliary switch S 2 is switched on Go to the next stage.
第四階段〔t 3~t 4〕:〔主開關S 1:off、輔助開關S 2:on、主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:on、整流二極體D 1:off、飛輪二極體D 2:on〕:請再一併參閱第六圖本發明之第四操作階段等效電路圖所示,本階段當輔助開關S 2切換為on時,達成ZVS,當輔助開關S 2之電流i 2變為正值時,輔助開關S 2的本體二極體D S2切換為off進入下一階段。 The fourth stage [ t 3 ~ t 4 ]: [main switch S 1 :off, auxiliary switch S 2 :on, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :on, rectifying diode D 1 :off, flywheel diode D 2 :on]: Please refer to the sixth circuit diagram of the fourth operation stage of the present invention as shown in the equivalent circuit diagram. switch S 2 is switched on, the ZVS reached, when the auxiliary switch S 2 of the current i 2 becomes positive, the auxiliary switch S 2 of the body diode D S 2 is switched off the next stage.
第五階段〔t 4~t 5〕:〔主開關S 1:off、輔助開關S 2:on、 主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:off、整流二極體D 1:off、飛輪二極體D 2:on〕:請再一併參閱第七圖本發明之第五操作階段等效電路圖所示,本階段當輔助開關S 2的本體二極體D S2切換為off時,該輔助開關S 2之電流i 2流經開關本體,當輔助開關S 2切換為off時進入下一階段。 The fifth stage [ t 4 ~ t 5 ]: [main switch S 1 :off, auxiliary switch S 2 :on, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :off, rectifying diode D 1 :off, flywheel diode D 2 :on]: Please refer to the seventh diagram for the fifth operation stage of the present invention as shown in the equivalent circuit diagram. when the switch S of the body diode D 2 S 2 switch is off, the auxiliary switch S 2 of the current i 2 flowing through the switch body, the next stage when the auxiliary switch S 2 is switched off.
第六階段〔t 5~t 6〕:〔主開關S 1:off、輔助開關S 2:off、主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:off、整流二極體D 1:off、飛輪二極體D 2:on〕:請再一併參閱第八圖本發明之第六操作階段等效電路圖所示,本階段當輔助開關S 2切換為off時,該輔助開關S 2跨壓v ds2線性上升,主開關S 1跨壓v ds1線性下降,當該變壓器(11)二次側之整流二極體D 1切換為on時進入下一階段。 The sixth stage [ t 5 ~ t 6 ]: [main switch S 1 :off, auxiliary switch S 2 :off, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :off, rectifying diode D 1 :off, flywheel diode D 2 :on]: Please refer to the eighth circuit diagram of the sixth operation stage of the present invention as shown in the equivalent circuit diagram. switching the switch S 2 is off, the voltage across the auxiliary switch S 2 v ds 2 rises linearly, the voltage across the main switch S 1 is decreased linearly v ds 1, when the rectifier (11) of the secondary side of the transformer switching diode D 1 Go to the next stage when it is on.
第七階段〔t 6~t 7〕:〔主開關S 1:off、輔助開關S 2:off、主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:off、整流二極體D 1:on、飛輪二極體D 2:on〕:請再一併參閱第九圖本發明之第七操作階段等效電路圖所示,本階段當整流二極體D 1切換為on時,該變壓器(11)二次側之二極體電流開始換向,輔助開關S 2跨壓v ds2共振上升,主開關S 1跨壓v ds1共振下降,當主開關S 1跨壓v ds1共振下降至零後,主開關S 1的本體二極體D S1切換為on時進入下一階段。 The seventh stage [ t 6 ~ t 7 ]: [main switch S 1 :off, auxiliary switch S 2 :off, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :off, rectifying diode D 1 :on, flywheel diode D 2 :on]: Please refer to the ninth diagram of the seventh operation stage of the present invention as shown in the equivalent circuit diagram, at this stage when rectifying When the diode D 1 is switched to on, the diode current on the secondary side of the transformer (11) starts to commutate, the auxiliary switch S 2 rises in resonance across the voltage v ds 2 , and the main switch S 1 decreases in resonance across the voltage v ds 1 . When the main switch S 1 is cooled down to zero across the voltage v ds 1 , the body diode D S 1 of the main switch S 1 is switched to on to enter the next stage.
第八階段〔t 7~t 8〕:〔主開關S 1:off、輔助開關S 2:off、 主開關S 1的本體二極體D S1:on、輔助開關S 2的本體二極體D S2:off、整流二極體D 1:on、飛輪二極體D 2:on〕:請再一併參閱第十圖本發明之第八操作階段等效電路圖所示,本階段當主開關S 1跨壓v ds1共振下降至零,該主開關S 1的本體二極體D S1切換為on,該主開關S 1隨時可以切換為on,達到ZVS,當主開關S 1切換為on時進入下一階段。 The eighth stage [ t 7 ~ t 8 ]: [main switch S 1 :off, auxiliary switch S 2 :off, body diode D S 1 :on of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :off, rectifying diode D 1 :on, flywheel diode D 2 :on]: Please refer to the eleventh figure. The equivalent circuit diagram of the eighth operation stage of the present invention is shown in this stage. switch S 1 is the voltage across the v ds 1 resonance drops to zero, the main switch S of the body 1 of the diode D S 1 is switched on, the main switch S 1 can always switch is on, to achieve the ZVS, when the main switch S 1 switches Go to the next stage when it is on.
第九階段〔t 8~t 9〕:〔主開關S 1:on、輔助開關S 2:off、主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:off、整流二極體D 1:on、飛輪二極體D 2:on〕:請再一併參閱第十一圖本發明之第九操作階段等效電路圖所示,本階段當主開關S 1切換為on時,達成ZVS,當變壓器(11)二次側之二極體電流換向完成,飛輪二極體D 2切換為off時進入下一階段。 Ninth stage [ t 8 ~ t 9 ]: [main switch S 1 :on, auxiliary switch S 2 :off, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :off, rectifying diode D 1 :on, flywheel diode D 2 :on]: Please refer to the eleventh figure for the ninth operation stage of the present invention as shown in the equivalent circuit diagram, this stage is When the main switch S 1 is switched to on, ZVS is reached. When the diode current reversal on the secondary side of the transformer (11) is completed and the flywheel diode D 2 is switched off, the next stage is entered.
第十階段〔t 9~t 10〕:〔主開關S 1:on、輔助開關S 2:off、主開關S 1的本體二極體D S1:off、輔助開關S 2的本體二極體D S2:off、整流二極體D 1:on、飛輪二極體D 2:on〕:請再一併參閱第十二圖本發明之第十操作階段等效電路圖所示,本階段當飛輪二極體D 2切換為off時,能量傳至負載負載R,主開關S 1切換為off時,回到第一階段。 The tenth stage [ t 9 ~ t 10 ]: [main switch S 1 :on, auxiliary switch S 2 :off, body diode D S 1 :off of main switch S 1 , body diode of auxiliary switch S 2 D S 2 :off, rectifying diode D 1 :on, flywheel diode D 2 :on]: Please refer to the twelfth figure. The equivalent circuit diagram of the tenth operation stage of the present invention is shown in this stage. When the flywheel diode D 2 is switched off, the energy is transmitted to the load R , and when the main switch S 1 is switched off, the first stage is returned.
依據上述電路動作分析,使用IsSpice模擬軟體及實作結果驗證上述之高降壓特性,以及主開關S 1與輔助開關S 2柔性切換性能。設定該轉換器(1)之相關參數為:輸入電源V in =400V、輸 出電壓V o =48V、輸出功率P o =100~400W、切換頻率f s =100kHz、變壓器匝數比n=1、變壓器一次側磁化電感L m =302μH、降壓電感L b =4μH、輸出電感L o =207μH、電容C B =33μF、電感L r =25μH、主開關S 1本體電容C S1=1250μF、輔助開關S 2本體電容C S2=1250μF、輸出電容C o =1000μF;以下以模擬波形與實作結果檢驗該轉換器(1)的特點: According to the above circuit operation analysis, the above-mentioned high buck characteristic and the flexible switching performance of the main switch S 1 and the auxiliary switch S 2 are verified using the IsSpice simulation software and the actual result. The relevant parameters of the converter (1) are set as: input power V in = 400V, output voltage V o = 48V, output power P o = 100~400W, switching frequency f s = 100kHz, transformer turns ratio n =1, Transformer primary side magnetizing inductance L m =302μH, step-down inductor L b =4μH, output inductance L o =207μH, capacitance C B =33μF, inductance L r =25μH, main switch S 1 body capacitance C S 1 =1250μF, auxiliary Switch S 2 body capacitance C S 2 =1250μF, output capacitance C o =1000μF; below test the characteristics of the converter (1) with analog waveform and implementation results:
A.電氣規格驗證:請再一併參閱第十三圖本發明之主開關驅動信號、輸入電源及輸出電壓的模擬波形圖與第十四圖本發明之主開關驅動信號、輸入電源及輸出電壓的實作波形圖所示,實作中導通比D=0.46時,輸出電壓V o 為48V;但若是以傳統非對稱半橋轉換器之電壓轉換比公式V o =D(1-D)V in/n,在n=1、D=0.46時,輸出電壓V o 為99.3V,,明顯無法降至訂定的電氣規格。 A. Electrical specification verification: Please refer to the thirteenth diagram for the main switch drive signal, input power supply and output voltage analog waveform diagram of the present invention and the fourteenth diagram of the main switch drive signal, input power supply and output voltage of the present invention. The implementation waveform diagram shows that when the conduction ratio D = 0.46, the output voltage V o is 48V; but if the voltage conversion ratio of the conventional asymmetric half-bridge converter is V 0 = D (1- D ) V i n / n , when n =1, D =0.46, the output voltage V o is 99.3V, which obviously cannot be reduced to the specified electrical specifications.
B.主開關S 1與輔助開關S 2柔切性能:請再一併參閱第十五圖本發明之主開關驅動信號與其跨壓模擬波形圖、第十六圖本發明之主開關驅動信號與其跨壓實作波形圖、第十七圖本發明之輔助開關驅動信號與其跨壓模擬波形圖及第十八圖本發明之輔助開關驅動信號與其跨壓實作波形圖所示,於滿載輸出功率P o =400W時,主開關S 1之跨壓v ds1下降至零後,驅動信號v gs1才切換為on,達到ZVS性能;輔助開關S 2之跨壓v ds2下降至零後,驅動信號v gs2才切換為on,達到ZVS性能,此外亦可知主開關S 1與輔助開關S 2之電壓應力皆為V in =400V。 B. Main switch S 1 and auxiliary switch S 2 flexible cutting performance: Please refer to the fifteenth figure of the present invention, the main switch driving signal and its cross-voltage analog waveform diagram, and the sixteenth embodiment of the main switch driving signal of the present invention Cross-pressing waveform diagram, the seventeenth embodiment of the present invention, the auxiliary switch drive signal and its cross-voltage analog waveform diagram and the eighteenth embodiment of the present invention, the auxiliary switch drive signal and its cross-voltage implementation waveform diagram, at full load output power after when P o = 400W, the main switch S cross voltage v of 1 ds 1 drops to zero, the drive signal v gs 1 was switched on, to achieve ZVS performance; auxiliary switch S across the voltage v 2 of ds 2 drops to a zero, The drive signal v gs 2 is switched to on to achieve the ZVS performance. It is also known that the voltage stress of the main switch S 1 and the auxiliary switch S 2 is V in = 400V.
C.高降壓性能驗證:請再一併參閱第十九圖本發明之降壓電感電流與輸出電感電流模擬波形圖及第二十圖本發明之降壓電感電流與輸出電感電流實作波形圖所示,加入降壓電感L b 能使轉換器(1)達到高降壓,係因為當主開關S 1切換為on時,二次側二極體電流開始換向,降壓電感L b 電流i Lb 開始上升,須等到降壓電感電流i Lb =i LO 時,二極體電流換向完畢,能量才能傳至負載R亦即二次側所得之實際導通責任比較主開關S 1之導通責任比小。 C. High-step-down performance verification: Please refer to the nineteenth figure for the buck inductor current and output inductor current analog waveform diagram and the twentieth figure. The buck inductor current and output inductor current implementation waveform of the present invention As shown in the figure, the addition of the buck inductor L b enables the converter (1) to reach a high buck because when the main switch S 1 is switched to on, the secondary side diode current begins to commutate, and the buck inductor L b When the current i Lb starts to rise, it must wait until the step-down inductor current i Lb = i LO , the diode current is commutated, and the energy can be transmitted to the load R, that is, the actual conduction responsibility obtained by the secondary side is compared with the conduction of the main switch S 1 . The responsibility ratio is small.
藉由以上所述,本發明之使用實施說明可知,本發明與現有技術手段相較之下,本發明主要係具有下列優點: From the above, the implementation description of the present invention shows that the present invention has the following advantages in comparison with the prior art means:
1.高降壓比:本發明利用降壓電感法達到高降壓,不需將導通責任比操作於極端窄小,亦不需使用匝數比n較大的變壓器,可降低變壓器的寄生元件,減少轉換器的突波。 1. High step-down ratio: The invention uses the step-down inductor method to achieve high voltage drop, does not need to operate the conduction duty ratio to be extremely narrow, and does not need to use a transformer with a larger turns ratio n, which can reduce the parasitic components of the transformer. , reduce the surge of the converter.
2.高轉換效率:本發明之主開關與輔助開關均可達成ZVS柔性切換,以降低切換損失,提高轉換器的轉換效率。 2. High conversion efficiency: Both the main switch and the auxiliary switch of the present invention can achieve ZVS flexible switching to reduce switching loss and improve conversion efficiency of the converter.
3.低電壓應力:本發明之主開關與輔助開關可分擔輸入電壓,使開關元件具有低電壓應力,適用於高電壓輸入應用。 3. Low voltage stress: The main switch and the auxiliary switch of the present invention can share the input voltage, so that the switching element has low voltage stress, and is suitable for high voltage input applications.
然而前述之實施例或圖式並非限定本發明之產品結構或使用方式,任何所屬技術領域中具有通常知識者之適當變化或修飾,皆應視為不脫離本發明之專利範疇。 However, the above-described embodiments or drawings are not intended to limit the structure or the use of the present invention, and any suitable variations or modifications of the invention will be apparent to those skilled in the art.
綜上所述,本發明實施例確能達到所預期之使用功效,又其 所揭露之具體構造,不僅未曾見諸於同類產品中,亦未曾公開於申請前,誠已完全符合專利法之規定與要求,爰依法提出發明專利之申請,懇請惠予審查,並賜准專利,則實感德便。 In summary, the embodiments of the present invention can achieve the expected use efficiency, and The specific structure disclosed has not only been seen in similar products, nor has it been disclosed before the application. Cheng has fully complied with the requirements and requirements of the Patent Law, and has filed an application for invention patents according to law. , it is really sensible.
(1)‧‧‧轉換器 (1)‧‧‧ converter
(11)‧‧‧變壓器 (11)‧‧‧Transformers
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Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4768141A (en) * | 1986-02-01 | 1988-08-30 | Guido Hubertus | D.c.-a.c. converter having an asymmetric half-bridge circuit |
TW200529541A (en) * | 2004-02-17 | 2005-09-01 | Spi Electronic Co Ltd | Asymmetric half-bridge forward converter |
TWM457354U (en) * | 2013-01-23 | 2013-07-11 | Chung Shan Inst Of Science | Bidirectional half-bridge DC-to-DC converter featuring asymmetric pulse control method |
TWI506931B (en) * | 2013-02-05 | 2015-11-01 | Univ Nat Kaohsiung Applied Sci | Single - stage high power zero - current detection frequency conversion asymmetric half - bridge converter |
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2016
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Patent Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4768141A (en) * | 1986-02-01 | 1988-08-30 | Guido Hubertus | D.c.-a.c. converter having an asymmetric half-bridge circuit |
TW200529541A (en) * | 2004-02-17 | 2005-09-01 | Spi Electronic Co Ltd | Asymmetric half-bridge forward converter |
TWM457354U (en) * | 2013-01-23 | 2013-07-11 | Chung Shan Inst Of Science | Bidirectional half-bridge DC-to-DC converter featuring asymmetric pulse control method |
TWI506931B (en) * | 2013-02-05 | 2015-11-01 | Univ Nat Kaohsiung Applied Sci | Single - stage high power zero - current detection frequency conversion asymmetric half - bridge converter |
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