TWI469480B - Single stage full bridge high power factor converter with oscillated commutation - Google Patents
Single stage full bridge high power factor converter with oscillated commutation Download PDFInfo
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
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本發明涉及一種電力電子技術應用裝置，具體地說，涉及一種單級高功因電力轉換裝置。The present invention relates to a power electronic technology application device, and in particular to a single-stage high power factor power conversion device.
近幾年來，功因修正電路之技術已得到大量研究，有了許多實現方案，其中比較成熟及廣為應用是兩級式之硬切高功因電力轉換裝置，其電路架構如第一圖所示。所謂的硬切，係指開關元件電路切換過程，開關元件電路兩端保有特定的電壓降，使切換過程造成可觀的損失。目前之傳統兩級式高功因電力轉換裝置需一級轉換器執行功因修正，另一級換流器執行直流/直流轉換，其中，轉換器、換流器內之開關元件電路均以硬切方式轉換切換為主，但是，硬切換式轉換器及換流器均有可觀的轉換或切換損失，除了轉換效率較差之外，其必須另須處理開關元件散熱之問題。而且，兩級式高功因電力轉換裝置用單一儲能電感，受限於高電流可能飽和之問題，高功率負載可能無法處理，高功因電力轉換裝置的儲能電感之電流iL 波形如第二圖所示。開關元件開關元件開關元件In recent years, the technology of the power correction circuit has been extensively studied, and there are many implementation solutions. Among them, the more mature and widely used is the two-stage hard-cut high-power-to-power conversion device, and its circuit architecture is as shown in the first figure. Show. The so-called hard cut refers to the switching process of the switching element circuit, and a specific voltage drop is maintained at both ends of the switching element circuit, causing considerable loss in the switching process. At present, the conventional two-stage high-power power conversion device requires a primary converter to perform power factor correction, and the other-stage converter performs DC/DC conversion, wherein the switching element circuits in the converter and the converter are hard cut. Switching switching is dominant, however, hard switching converters and converters have considerable switching or switching losses. In addition to poor conversion efficiency, they must also deal with the problem of heat dissipation of switching components. Moreover, the two-stage high-power power conversion device uses a single energy storage inductor, which is limited by the problem that high current may be saturated. The high-power load may not be able to be processed, and the high power due to the energy storage inductance of the power conversion device i L waveform The second picture shows. Switching element switching element switching element
本發明之主要目的在於提供一種單級高功因電力轉換裝置，解決現有電力轉換裝置轉換效率差、無法處理高功率負載及切換損失之問題。The main object of the present invention is to provide a single-stage high-power-conversion power conversion device, which solves the problem that the conventional power conversion device has poor conversion efficiency and cannot handle high-power load and switching loss.
為了解決上述現有技術問題，本發明提供了一種單級高功因電力轉換裝置，與電源和負載相連接，所述裝置的電路包括有第一儲能電感和第二儲能電感，所述第一儲能電感及第二儲能電感分別連接至同一全橋諧振換向式電路，所述全橋諧振式換向電路還並聯有儲能電容。In order to solve the above prior art problems, the present invention provides a single-stage high-power-dependent power conversion device connected to a power source and a load, the circuit of the device including a first energy storage inductor and a second energy storage inductor, A storage inductor and a second energy storage inductor are respectively connected to the same full-bridge resonant commutating circuit, and the full-bridge resonant commutator circuit further has a storage capacitor in parallel.
進一步地，所述裝置的電路還包括有電源整流電路，用於對電源電流進行濾波，所述電源整流電路包括與電源並聯的整流電容和與電源串聯的整流電感。Further, the circuit of the device further includes a power rectifying circuit for filtering the power supply current, the power rectifying circuit comprising a rectifying capacitor connected in parallel with the power source and a rectifying inductor connected in series with the power source.
本發明的有益效果為：The beneficial effects of the invention are:
(1)本發明相較於現有兩級式電力轉換裝置省去一級轉換器，效率可提升；(1) Compared with the existing two-stage power conversion device, the present invention saves the first-stage converter, and the efficiency can be improved;
(2)本發明的電路直接引用原全橋諧振式換向器開關元件，同時作為功因修正切換開關元件，具有單級高功因修正(Power Factor Correction)之功能，改善功因之問題，且利用雙電感分攤輸入轉換器之電流，儲放能電感不易飽和，可使用在較大功率輸出之電路；(2) The circuit of the present invention directly references the original full-bridge resonant commutator switching element, and simultaneously functions as a power factor correction switching switch element, and has a single-stage power factor correction function to improve the cause of the function. And the dual inductor is used to share the current of the input converter, and the storage and discharge inductor is not easy to be saturated, and can be used in a circuit with a larger power output;
(3)本發明的切換開關元件具有零電壓切換ZVS(Zero Voltage Switching)之功能，此功能可減少開關元件上損失，提升電路效率，並減少開關元件發熱；(3) The switching element of the present invention has a function of zero voltage switching ZVS (Zero Voltage Switching), which can reduce loss on the switching element, improve circuit efficiency, and reduce heating of the switching element;
(4)本發明的電路架構具有將市電低頻轉換成高頻之功能，降低高次諧波之干擾。(4) The circuit architecture of the present invention has the function of converting the commercial low frequency into a high frequency, and reducing the interference of higher harmonics.
(5)本發明外加兩個電感之儲放能元件而可執行輸入電源高功因操作，且本發明之負載並聯於該儲能電容，負載端可直接驅動直流元件，連接於該負載端之逆 止二極體可保護電路免於負載或儲能電容之能量回衝而可能造成之毀損，故賦予本發明具備極高的穩定性。(5) The present invention is applied with two inductor storage and discharge components to perform high power operation of the input power source, and the load of the present invention is connected in parallel with the storage capacitor, and the load terminal can directly drive the DC component and is connected to the load terminal. inverse The stop diode protects the circuit from the energy backlash of the load or the storage capacitor and can cause damage, thus giving the present invention extremely high stability.
於to
下面結合附圖和具體實施例對本發明作進一步說明，以使本領域的技術人員可以更好地理解本發明並能予以實施，但所舉實施例不作為對本發明的限定。The present invention will be further described in conjunction with the accompanying drawings and specific embodiments, which are to be understood by those skilled in the art.
第三圖所示為本發明單級高功因電力轉換裝置的電路架構示意圖，從圖中可以看出，本發明將現有轉換裝置的切換式轉換器和換流器集成整合為一，利用二儲能電感分攤輸入轉換裝置之電流，解決既有技術單一儲能電感容易飽和而限制使用功率輸出之問題，使本較佳實施例具備較大功率輸出之電路之技術功效。The third figure shows a schematic diagram of the circuit architecture of the single-stage high-power-converting power conversion device of the present invention. As can be seen from the figure, the present invention integrates the switching converter and the converter of the existing conversion device into one, using two The energy storage inductor distributes the current of the input conversion device to solve the problem that the prior art single energy storage inductor is easy to be saturated and the power output is limited, so that the preferred embodiment has the technical effect of the circuit with larger power output.
第四圖為本發明單級高功因電力轉換裝置的較佳實施例電路圖，本實施例單級高功因電力轉換裝置與一電源AC和一負載Load相連接，該單級高功因電力轉換裝置的電路包含一第一儲能電感L1和一第二儲能電感L2、一全橋諧振式換向電路S1~S4、D1~D4、一諧振式換向電路C3、L4及一儲能電容C1，該第一儲能電感L1及該第二儲能電感L2分別連接至該全橋諧振式換向電路與該整流電路之間。該儲能電容C1連接於該全橋諧振式換向電路與該負載之間，其執行儲放能工作。The fourth figure is a circuit diagram of a preferred embodiment of the single-stage high-power-dependent power conversion device of the present invention. In this embodiment, the single-stage high-power-to-power conversion device is connected to a power source AC and a load load, and the single-stage high power factor power is connected. The circuit of the conversion device comprises a first energy storage inductor L1 and a second energy storage inductor L2, a full bridge resonant commutation circuit S1~S4, D1~D4, a resonant commutating circuit C3, L4 and an energy storage device. The capacitor C1, the first energy storage inductor L1 and the second energy storage inductor L2 are respectively connected between the full bridge resonant commutation circuit and the rectifier circuit. The storage capacitor C1 is connected between the full-bridge resonant commutation circuit and the load, and performs a storage and discharge operation.
該電源與該單級高功因電力轉換裝置之間並聯一電源整流電路，用於對該電源之輸出交流電力進行初步整 流後輸出，該電源整流電路包括與該電源並聯的一整流電容C2、與該電源串聯的一整流電感L3及一整流二極體D5。該整流二級體D5係用於初步將該電源AC所輸出之交流電源轉換進行整流後輸出至該單級高功因電力轉換裝置。需要特別指出的是，該整流電路的實現並不僅限於此，本領域的技術人員還可選用其它任一本領域的初步整流電路技術來實現濾波、整流和對電路的保護。A power rectifier circuit is connected between the power source and the single-stage high-power-converting power conversion device for initializing the output AC power of the power source After the current output, the power rectifier circuit includes a rectifying capacitor C2 connected in parallel with the power source, a rectifying inductor L3 connected in series with the power source, and a rectifying diode D5. The rectifying diode D5 is used for initially rectifying the AC power output from the power source AC and outputting the same to the single-stage high power factor power conversion device. It should be particularly noted that the implementation of the rectifier circuit is not limited thereto, and those skilled in the art may also select any other preliminary rectifier circuit technology in the field to implement filtering, rectification, and protection of the circuit.
該全橋諧振式換向電路包括呈全橋式連接之四個主動開關組，每個該主動開關組包含並聯之一開關元件及一二極體，該二極體與該開關元件可以是內嵌(embedded)一個二極體之場效電晶體(MOSFET)，或為等效上不具有內嵌二極體特性之電晶體(例如雙極電晶體BJT等)再並聯一外部二極體而組成該主動開關組。換言之，每個主動開關組等效為一個二極體以及一個開關元件之並聯，亦即，該全橋式連接之四個電晶體開關元件，其等效電路為包含依次連接之第一二極體D1、第二二極體D2、第三二極體D3及第四二極體D4，該第一二極體D1與該第二二極體D2之陰極及陽極分別相連，該第三二極體D3及該第四二極體D4之陽極與陰極分別相互連接，該第一二極體D1及該第三二極體D3串連，該第二二極體D2及該第四二極體D4串連；每個二極體D1~D4各並聯一開關元件S1~S4，該第一二極體D1與該開關元件S1並聯，第二二極體D2與開關元件S2並聯，第三二極體D3與開關元件S3並聯，第四 二極體D4與開關元件S4並聯。The full-bridge resonant commutation circuit includes four active switch groups connected in a full bridge, each of the active switch groups including one switching element and one diode in parallel, and the diode and the switching element can be internal Embedding a diode field effect transistor (MOSFET), or a transistor that is equivalent to having no embedded diode characteristics (eg, bipolar transistor BJT, etc.) and then paralleling an external diode The active switch group is composed. In other words, each active switch group is equivalent to a diode and a parallel connection of a switching element, that is, the four transistor switching elements of the full bridge connection, the equivalent circuit of which includes the first two poles connected in sequence a body D1, a second diode D2, a third diode D3, and a fourth diode D4. The first diode D1 is connected to the cathode and the anode of the second diode D2, respectively. The anode D3 and the anode and cathode of the fourth diode D4 are respectively connected to each other, and the first diode D1 and the third diode D3 are connected in series, and the second diode D2 and the fourth diode The body D4 is connected in series; each of the diodes D1 to D4 is connected in parallel with a switching element S1~S4, the first diode D1 is connected in parallel with the switching element S1, and the second diode D2 is connected in parallel with the switching element S2, and the third Diode D3 is connected in parallel with switching element S3, fourth The diode D4 is connected in parallel with the switching element S4.
該第一儲能電感L1一端連接於第一二極體D1和第三二極體D3連接節點之間，另一端連接至整流二極體D5；該第二儲能電感L2一端連接於該第二二極體D2和該第四二極體D4連接節點之間，另一端連接至該整流二級體D5。One end of the first energy storage inductor L1 is connected between the connection node of the first diode D1 and the third diode D3, and the other end is connected to the rectifying diode D5; one end of the second energy storage inductor L2 is connected to the first The second diode D2 and the fourth diode D4 are connected between the nodes, and the other end is connected to the rectifying diode D5.
該儲能電容C1串連一逆止二極體D6後與該全橋諧振式換向電路並接，該逆止二極體D6之兩端分別與該第三二極體D3和第四二極體D4之連接節點與該儲能電容C1連接，該儲能電容C1之另一端連接於第一二極體D1和第二二極體D2之連接節點，該逆止二極體D6主要作為防止該儲能電容C1或該負載之電能回衝至該全橋諧振式換向電路，造成電氣性能上之毀損。The storage capacitor C1 is connected in series with a back-up diode D6 and is connected to the full-bridge resonant commutation circuit. The two ends of the back-stop diode D6 are respectively connected to the third diode D3 and the fourth two. The connection node of the pole body D4 is connected to the storage capacitor C1, and the other end of the storage capacitor C1 is connected to the connection node of the first diode D1 and the second diode D2, and the backstop diode D6 is mainly used as The energy storage capacitor C1 or the energy of the load is prevented from being backflushed to the full-bridge resonant commutation circuit, causing damage in electrical performance.
該諧振換向電路L4、C3之一端連接於該第一第一二極體D1及該第三二極體D3之連接節點，其另一端連接於該第二二極體D2和第四二極體D4之間；本實施例之該諧振換向電路包含串接之一諧振電感L4和一諧振電容C3，其係設計工作於電感負載特性，使該全橋諧振式換向電路之各開關元件S1~S4可達到零電壓切換，藉以減少各開關元件S1~S4切換過程之損失。One end of the resonant commutation circuit L4, C3 is connected to the connection node of the first first diode D1 and the third diode D3, and the other end is connected to the second diode D2 and the fourth diode The resonant commutation circuit of the embodiment includes a resonant inductor L4 and a resonant capacitor C3 connected in series, and is designed to operate in an inductive load characteristic to make each switching component of the full bridge resonant commutating circuit S1~S4 can achieve zero voltage switching, thereby reducing the loss of switching process of each switching element S1~S4.
該全橋諧振式換流電路之四個開關元件S1~S4之整合，使該全橋諧振式換流電路可執行直流/直流之轉換功能，且各開關元件S1~S4以對稱方式觸發，亦即該開關元件S1與該開關元件S4同步開啟、該開關元件S2與該開關元件S3同步開啟，但該開關元件S1與該 開關元件S2(或S3、S4)交互切換不同時導通(開啟)，各開關元件之切換觸波形如第五圖所示，其中，Vgs1 、Vgs2 、Vgs3 、Vgs4 分別為開關元件S1~S4之觸發訊號電壓，係指控制該開關元件S1~S4導通之訊號，iL1 為流經第一儲能電感L1的電流，iL2 為流經第二儲能電感L2的電流；依據第五圖之波形可知，利用該開關元件S1及開關元件S2之交錯導通，使該第一儲能電感L1與該第二儲能電感L2之電流分別操作於不連續模式，且開關元件S1,S4以及該開關元件S2,S3之間設有一無開關元件導通區間(dead time)，其係為了避免該開關元件S1及該開關元件S4、該開關元件S2及該開關元件S3有同時開啟之狀況。另外，由第五圖亦可看出該開關元件S2、S3與該開關元件S1、S4導通前該二極體D2、D3與該二極體D1、D4先導通，該開關元件S2S3與該開關元件S1 S4具零電壓導通切換，降低開關元件發熱量。The integration of the four switching elements S1~S4 of the full-bridge resonant converter circuit enables the full-bridge resonant converter circuit to perform a DC/DC conversion function, and each of the switching elements S1~S4 is triggered in a symmetrical manner. That is, the switching element S1 is turned on synchronously with the switching element S4, and the switching element S2 is turned on synchronously with the switching element S3, but the switching element S1 and the switching element S2 (or S3, S4) are not switched on at the same time (on). The switching waveform of each switching element is as shown in FIG. 5 , wherein V gs1 , V gs2 , V gs3 , and V gs4 are trigger signal voltages of the switching elements S1 to S4 respectively, and the switching elements S1 to S4 are controlled to be turned on. The signal, i L1 is the current flowing through the first energy storage inductor L1, and i L2 is the current flowing through the second energy storage inductor L2; according to the waveform of the fifth figure, the staggered conduction of the switching element S1 and the switching element S2 is used. The currents of the first energy storage inductor L1 and the second energy storage inductor L2 are respectively operated in a discontinuous mode, and a non-switching component conduction interval is provided between the switching elements S1, S4 and the switching elements S2, S3 (dead Time), in order to avoid the switching element S1 and The switching element S4, and the switching element S2 of the switching element S3 is turned on at the same time it has the situation. In addition, it can be seen from the fifth figure that the diodes D2 and D3 and the diodes D1 and D4 are turned on before the switching elements S2 and S3 and the switching elements S1 and S4 are turned on, and the switching element S2S3 and the switch are turned on. The component S1 S4 has a zero voltage conduction switch to reduce the heat generated by the switching element.
請配合參考第六圖、第七圖，透過配置兩個儲能電感L1、L2及該全橋諧振式換向電路之各開關元件S1~S4之交錯導通，使該整流電路之輸出電流iRO 及輸出峰值電流iROP 可如第六圖所式，由於該第一儲能電感L1及該第二儲能電感L2隨各開關元件之切換控制，產生相位交錯互補之電流iL1 與iL2 (該第一儲能電感L1之電感電流iL1 標示為實線，該第二儲能電感L1之電感電流iL2 標示為虛線)，使該電感電流iL1 與iL2 之合成電流為每切換週期之峰值電流恰為一弦波峰包之峰值，使最終於該整 流電路輸出之合成電流iRO 已經非常接近弦波，如此，使後續的高頻雜訊去除更為容易、簡便；其中，第七圖所示為電路各主要元件上之電壓或電流波形，VAC 代表該電源兩端的電壓，VRO 和iRO 該整流電路輸出側之電壓和電流，is 為濾波後之交流電源輸入電流，iAC 為濾波前之交流電源輸入電流。Please refer to the sixth and seventh figures to configure the output current i RO of the rectifier circuit by configuring the two storage inductors L1 and L2 and the interleaving conduction of the switching elements S1 to S4 of the full-bridge resonant commutation circuit. And the output peak current i ROP can be as shown in the sixth figure. Since the first energy storage inductor L1 and the second energy storage inductor L2 are controlled by switching of the switching elements, the phases staggered complementary currents i L1 and i L2 are generated ( The inductor current i L1 of the first energy storage inductor L1 is indicated as a solid line, and the inductor current i L2 of the second energy storage inductor L1 is indicated by a dashed line), so that the combined current of the inductor currents i L1 and i L2 is every switching period. The peak current is exactly the peak value of the one-string peak packet, so that the resultant current i RO finally outputted to the rectifier circuit is very close to the sine wave, thus making the subsequent high-frequency noise removal easier and simpler; The figure shows the voltage or current waveform on each main component of the circuit, V AC represents the voltage across the power supply, V RO and i RO the voltage and current on the output side of the rectifier circuit, and i s is the filtered AC power input current. i AC is the AC power input before filtering Current.
更進一步說明之，本實施例之單級高功因電力轉換裝置的動作模式如第八圖~第十三圖，說明如下：To further illustrate, the operation modes of the single-stage high-power-dependent power conversion device of the present embodiment are as follows: FIG. 8 to FIG.
(1)配合參考第八圖，開關元件S1與S4導通，該第一儲能電感L1進行儲能，該第二儲能電感L2可經過該開關元件S4或該第四二極體D4對該儲能電容C1進行釋能，此時該諧振換向電路L4、C3對該儲能電容C1充電。(1) With reference to the eighth figure, the switching elements S1 and S4 are turned on, the first energy storage inductor L1 performs energy storage, and the second energy storage inductor L2 can pass the switching element S4 or the fourth diode D4. The storage capacitor C1 performs energy release, and at this time, the resonant commutation circuits L4 and C3 charge the storage capacitor C1.
(2)配合參考第九圖，該開關元件S1與S4繼續導通，該第一儲能電感L1持續儲能，該第二儲能電感之電感電流L2經過該開關元件S4或該第四二極體D4對該儲能電容C1釋能，此時諧振換向電路經由該第三二極體D3對該儲能電容C1充電。(2) With reference to the ninth figure, the switching elements S1 and S4 continue to be turned on, the first energy storage inductor L1 continues to store energy, and the inductor current L2 of the second energy storage inductor passes through the switching element S4 or the fourth diode The body D4 releases the storage capacitor C1, and the resonant commutation circuit charges the storage capacitor C1 via the third diode D3.
(3)配合參考第十圖，該開關元件S1~S4截止，電路進入無開關元件導通區間，在開關元件S2、S3導通之前，電流先流經第三二極體D3、該諧振換向電路及該第二二極體D2；在下個模式時再導通該開關元件S3、S2，藉以達成零電壓切換之效果。(3) With reference to the tenth figure, the switching elements S1 to S4 are turned off, and the circuit enters the conduction interval of the non-switching element. Before the switching elements S2 and S3 are turned on, the current first flows through the third diode D3, and the resonant commutation circuit And the second diode D2; the switching elements S3, S2 are turned on again in the next mode, thereby achieving the effect of zero voltage switching.
(4)配合參考第十一圖，該開關元件S2與S3導 通，該第二儲能電感L2開始儲能，電流經過該第一儲能電感L1流經開關元件S3或第三二極體D3對儲能電容C1充電或經串聯諧振換向電路做釋能，該諧振換向電路經由開關元件S3或第三二極體D3對該儲能電容C1充電。(4) With reference to the eleventh figure, the switching elements S2 and S3 lead The second energy storage inductor L2 starts to store energy, and the current flows through the first energy storage inductor L1 through the switching element S3 or the third diode D3 to charge the storage capacitor C1 or to discharge through the series resonant commutation circuit. The resonant commutation circuit charges the storage capacitor C1 via the switching element S3 or the third diode D3.
(5)配合參考第十二圖，該開關元件S2與S3繼續導通，該第二儲能電感L2繼續儲能，電流經該第一儲能電感L1、D3對該儲能電容C1釋能，此時諧振換向電路經過第四二極體D4對該儲能電容C1充電。(5) With reference to the twelfth figure, the switching elements S2 and S3 continue to be turned on, the second energy storage inductor L2 continues to store energy, and the current is discharged to the storage capacitor C1 via the first energy storage inductors L1, D3. At this time, the resonant commutation circuit charges the storage capacitor C1 via the fourth diode D4.
(6)配合參考第十三圖，該開關元件S1~S4截止，此時諧振換向電路在開關元件S1、S4導通之前，電流先流經第一、四二極體D1、D4；並且該開關元件S1、S4於下個模式導通，即可達到零電壓切換。(6) With reference to the thirteenth diagram, the switching elements S1 to S4 are turned off, and at this time, the resonant commutation circuit flows through the first and fourth diodes D1 and D4 before the switching elements S1 and S4 are turned on; The switching elements S1 and S4 are turned on in the next mode to achieve zero voltage switching.
由前述說明可知，本實施例可以達成之技術功效包含：It can be seen from the foregoing description that the technical effects that can be achieved in this embodiment include:
1.本發明為單級高功因修正電路，構造簡單，省去傳統雙級電路效率不佳的問題。1. The present invention is a single-stage high power factor correction circuit, which has a simple structure and saves the problem of poor efficiency of the conventional two-stage circuit.
2.設有兩個儲能電感，大幅提昇輸出功率，解決既有技術使用單一電感容易飽和之問題。2. There are two energy storage inductors, which greatly increase the output power and solve the problem that the existing technology is easy to saturate with a single inductor.
3.本發明獨創提出在零電壓切換之全橋諧振式換向電路，透過控制開關元件之切換，使該全橋換流電路同時作為功因修正及轉換器，達到最佳功因及轉換效果。3. The invention uniquely proposes a full-bridge resonant commutating circuit with zero voltage switching, and by switching the control switching elements, the full-bridge commutation circuit is simultaneously used as a power factor correction and converter to achieve optimal power factor and conversion effect. .
4.本發明最終之濾波前之輸出電流僅剩於微量高頻 諧波干擾且波形接近弦波，故可透過更簡單的濾波(相對較低的電感、電容)，即可達到優異、穩定的輸出。4. The output current before the final filtering of the present invention is only left in the trace high frequency Harmonic interference and the waveform is close to the sine wave, so the simpler filter (relatively lower inductance, capacitance) can achieve excellent and stable output.
5.本發明外加兩個電感之儲放能元件而可執行輸入電源高功因操作，且本發明之負載並聯於該儲能電容，負載端可直接驅動直流元件，連接於該負載端之逆止二極體可保護電路免於負載或儲能電容之能量回衝而可能造成之毀損，故賦予本發明具備極高的穩定性。等。5. The present invention adds two inductive storage and discharge elements to perform high power operation of the input power source, and the load of the present invention is connected in parallel with the storage capacitor, and the load end can directly drive the DC component and is connected to the inverse of the load terminal. The stop diode protects the circuit from the energy backlash of the load or the storage capacitor and can cause damage, thus giving the present invention extremely high stability. Wait.
以上所述實施例僅是為充分說明本發明而所舉的較佳的實施例，本發明的保護範圍不限於此。本技術領域的技術人員在本發明基礎上所作的等同替代或變換，均在本發明的保護範圍之內。本發明的保護範圍以申請專利範圍為准。The embodiments described above are merely preferred embodiments for the purpose of fully illustrating the invention, and the scope of the invention is not limited thereto. Equivalent substitutions or modifications made by those skilled in the art based on the present invention are within the scope of the present invention. The scope of protection of the present invention is based on the scope of the patent application.
L1‧‧‧第一儲能電感L1‧‧‧First energy storage inductor
D1‧‧‧第一二極體D1‧‧‧First Diode
L2‧‧‧第二儲能電感L2‧‧‧Second energy storage inductor
D2‧‧‧第二二極體D2‧‧‧ second diode
L3‧‧‧整流電感L3‧‧‧Rectifier inductor
D3‧‧‧第三二極體D3‧‧‧ third diode
L4‧‧‧諧振電感L4‧‧‧Resonant Inductance
D4‧‧‧第四二極體D4‧‧‧ fourth diode
C1‧‧‧儲能電容C1‧‧‧ storage capacitor
D5‧‧‧整流二級體D5‧‧‧Rectified secondary body
C2‧‧‧整流電容C2‧‧‧Rectifier
S1‧‧‧開關元件S1‧‧‧ switching components
C3‧‧‧諧振電容C3‧‧‧Resonance Capacitor
S2‧‧‧開關元件S2‧‧‧ switching components
D6‧‧‧逆止二極體D6‧‧‧Backstop diode
S3‧‧‧開關元件S3‧‧‧Switching elements
S4‧‧‧開關元件S4‧‧‧ switching components
第一圖是現有兩級式高功因電力轉換裝置之電路架構示意圖。The first figure is a schematic diagram of the circuit structure of the existing two-stage high power factor power conversion device.
第二圖是現有兩級式高功因電力轉換裝置的儲能電感之電流波形圖。The second figure is a current waveform diagram of the energy storage inductor of the existing two-stage high power factor power conversion device.
第三圖是本發明的電路架構示意圖。The third figure is a schematic diagram of the circuit architecture of the present invention.
第四圖是本發明的電路圖。The fourth figure is a circuit diagram of the present invention.
第五圖是本發明的部分電路元件之電壓電流波形圖。The fifth figure is a waveform diagram of voltage and current of some circuit elements of the present invention.
第六圖是本發明的兩個儲能電感之電流波形圖及合成波形圖。The sixth figure is a current waveform diagram and a composite waveform diagram of two energy storage inductors of the present invention.
第七圖是本發明的電路主要元件之電壓或電流波形 圖。Figure 7 is a voltage or current waveform of the main components of the circuit of the present invention. Figure.
第八圖和第九圖是本發明的電路在開關元件S1及S4導通時動作模式示意圖。The eighth and ninth diagrams are schematic diagrams showing the operation modes of the circuit of the present invention when the switching elements S1 and S4 are turned on.
第十圖是本發明的電路在開關元件S1及S4截止時動作模式示意圖。The tenth diagram is a schematic view showing the operation mode of the circuit of the present invention when the switching elements S1 and S4 are turned off.
第十一圖和第十二圖是本發明的電路在開關元件S2及S3導通時動作模式示意圖。11 and 12 are schematic views showing the operation modes of the circuit of the present invention when the switching elements S2 and S3 are turned on.
第十三圖是本發明的電路在開關元件S2及S3截止時動作模式示意圖。Fig. 13 is a view showing the operation mode of the circuit of the present invention when the switching elements S2 and S3 are turned off.
L1‧‧‧第一儲能電感L1‧‧‧First energy storage inductor
D1‧‧‧第一二極體D1‧‧‧First Diode
L2‧‧‧第二儲能電感L2‧‧‧Second energy storage inductor
D2‧‧‧第二二極體D2‧‧‧ second diode
L3‧‧‧整流電感L3‧‧‧Rectifier inductor
D3‧‧‧第三二極體D3‧‧‧ third diode
L4‧‧‧諧振電感L4‧‧‧Resonant Inductance
D4‧‧‧第四二極體D4‧‧‧ fourth diode
C1‧‧‧儲能電容C1‧‧‧ storage capacitor
D5‧‧‧整流二極體D5‧‧‧Rected Diode
C2‧‧‧整流電容C2‧‧‧Rectifier
S1‧‧‧開關元件S1‧‧‧ switching components
C3‧‧‧諧振電容C3‧‧‧Resonance Capacitor
S2‧‧‧開關元件S2‧‧‧ switching components
D6‧‧‧逆止二極體D6‧‧‧Backstop diode
S3‧‧‧開關元件S3‧‧‧Switching elements
S4‧‧‧開關元件S4‧‧‧ switching components
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Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4471269A (en) * | 1981-12-14 | 1984-09-11 | U.S. Philips Corporation | Circuit arrangement for operating a high-pressure gas discharge lamp |
| CN1080531C (en) * | 1992-09-22 | 2002-03-06 | 松下电工株式会社 | Discharge lamp lighting device |
| TWI319692B (en) * | 2006-08-08 | 2010-01-11 | Univ Nat Cheng Kung | A self-oscillating full-bridge electronic ballast |
| TWI327043B (en) * | 2006-07-20 | 2010-07-01 | Ind Tech Res Inst |
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Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4471269A (en) * | 1981-12-14 | 1984-09-11 | U.S. Philips Corporation | Circuit arrangement for operating a high-pressure gas discharge lamp |
| CN1080531C (en) * | 1992-09-22 | 2002-03-06 | 松下电工株式会社 | Discharge lamp lighting device |
| TWI327043B (en) * | 2006-07-20 | 2010-07-01 | Ind Tech Res Inst | |
| TWI319692B (en) * | 2006-08-08 | 2010-01-11 | Univ Nat Cheng Kung | A self-oscillating full-bridge electronic ballast |
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