1355795 九、發明說明： 【發明所屬之技術領域】 本發明係有關一種利用峰值電流模式控制驰返式轉 .換器充電之磁化機，尤指一種使該磁化機之一線圈組件 -與該充電裝i電賴，用則吏該線圈組件與一磁性組件 互感產生一磁力而對一待磁化件進行磁化作用，該充電 #裝置包括，該充電裝置包括一整流電路、一馳返式轉換 益、一電流控制模組及一控制元件，俾使該控制元件控 制電源輪出迴路與該線圈組件之間的電源通路者。 【先前技術】 永久磁鐵經常被廣泛使用許多需要產生磁場之設 備，例如永磁式馬達。其需求量日益增加。磁化永久磁 φ的激磁系統有四種方式：永久磁鐵來磁化、直流電源來 磁化、半波磁化以及電容放電磁化等。 欲將一材料磁化使其有相當大之殘磁，必須在磁化 ««又施上產生足夠大之磁場強度使其飽和，而根據經驗法 則大約為材料本身磁場強度的五倍以上，這需要相當大 的電壓及電流。對於激磁系統而言，間歇性產生高電壓 大電流將會產生許多問題。 利用電容放電脈衝磁化有較多優點，它所需的電壓 1355795 及電流相對較低，目前在工業界被廣泛使用。它的電路、 磁場以及磁化設施的熱流等都曾被探討。 然而傳統電容放電脈衝磁化系仍有下列兩項缺點： • I它需要一高電壓大容量之變壓器以及大容量之整流二 ' 極體’而變壓器往往在3KVA以上，它暨昂貴又笨重 2.閘流體之開關動作將產生諧波，而電容充電時亦產生瞬 φ 間電流突波都會影響鄰近電力系統。 本發明使用一交直流驰返式轉換器來取代前述之變壓器， 它對電容的充電速度雖不如使用變壓器，但仍足夠應付一般之 需求。它降低整個系統之體積、重量以及功率需求及損耗。同 時這馳返式轉換器使用電流控制模式（current m〇de control )，它對電容充電以一波接一波方式進行，如此將可抑 制突波產生。 典型之電今放電脈衝磁化系統線路如第一圖所示。其激 磁動作乃藉由一繞於軛鐵上之線圈來產生磁場並將軛鐵内之材 “料磁化。而這部分稱為磁化設施（magnetizing fixture)，它 .在電路上以一負載電阻（RL)及串聯一線圈組件（L1)來表示。並 可用三個階段來描述其運作： 1、電容器（C2)充電階段：當scri導通時，電容器（C2)首 先經由整流電路（41)整流後之直流予以充電，其極性如第一圖 1355795 所示，這過程大概需數秒鐘，當充電完成後SCR1關閉。 2、 磁化階段：這階段開始必須先觸發SCR2導通，於是儲 存於電容器（C2)之能量將轉換至負載電阻（RL)-線圈組件（L1) 負載亦即磁化設施，藉以磁化軛鐵内之材料。這時恢復二極體 (D3)是不導通的，當電感電流到達最大值後開始減少時這階段 就結束。 3、 電感放電階段：當電感電流開始減小時電感電壓反向 而使得恢復二極體（D3)開始導通，而恢復二極體（D3)導通後， 電容電壓降為零而SCR2關閉。這階段線圈組件（L1)之電感能 量消耗在負載電阻（RL)上面，一直到電流降為零。 上述習用磁化機於實施時會產生下列缺失： (1) 電容充電階段，初期由於電容幾近短路，它將於變壓器 一次侧造成電流突波影響週遭之電氣設備，同時這也使變壓器 以及整流用之二極體容量必須相當大以免燒毁。 (2) 導通瞬間電流大，所以需要限流電阻（R2)，而且 效率低、成本較高，且隔離變壓器額定容量大，加上其 輸出電壓高達約數千伏特左右，因此，該習用結構必須 使用體積大、重量笨重的隔離變壓器。 (3)因為利用相位角觸發SCR (其觸發電流高達約數 安培），所以控制輸出電壓時會產生大量高諧波，因而造 1355795 成電磁干擾。 (4)此外，大量諧波較容易注入電力系統，進而影響 鄰近地區用戶之供電品質，且高諧波電流所形成之磁場 - 對同步或感應電動機或磁化機，不但無法提供實值轉矩 Torque，即扭力或驅動力，反而產生反效果的逆向轉矩， 進而減低電動機或磁化機之機械運轉效能；同時亦會增 _加變壓器的鐵損（渦流損及磁滯損）及銅損，造成溫度 異常上昇或引起鐵心與繞組之共振，並且發出噪音的響 聲等諸多的缺失。 參考文獻： (1) Ravell，GH,” An Over.view of Magnet Process” .Electrical Electronics Insulation Conference, 1 995,and Electrical Manufacturing& Coil Winding Conference. Proceeding,Sep.,1 995.1355795 IX. Description of the Invention: [Technical Field] The present invention relates to a magnetizer for controlling a regenerative converter using a peak current mode, and more particularly to a coil assembly of the magnetizer - and the charging The charging device comprises a magnetic force for magnetizing a magnetic component to be magnetized, and the charging device comprises a rectifying circuit and a regenerative conversion benefit. A current control module and a control component enable the control component to control a power path between the power supply circuit and the coil assembly. [Prior Art] Permanent magnets are often widely used in many devices that require a magnetic field, such as a permanent magnet motor. Its demand is increasing. There are four ways to magnetize the permanent magnet φ excitation system: magnetization of permanent magnets, magnetization of DC power supplies, half-wave magnetization, and electromagnetic discharge of capacitors. In order to magnetize a material to have a considerable residual magnetism, it must be magnetized to produce a sufficiently large magnetic field strength to saturate it, and according to the rule of thumb, it is about five times more than the magnetic field strength of the material itself. Large voltage and current. For the excitation system, intermittent generation of high voltage and large current will cause many problems. The use of capacitor discharge pulse magnetization has many advantages. It requires a voltage of 1355795 and a relatively low current, and is currently widely used in the industry. Its circuits, magnetic fields, and heat flow in magnetizing facilities have all been explored. However, the traditional capacitor discharge pulse magnetization system still has the following two disadvantages: • It requires a high voltage and large capacity transformer and a large-capacity rectifying two 'pole body' and the transformer is often above 3KVA, which is expensive and bulky. The switching action of the fluid will generate harmonics, and the current surge generated during the charging of the capacitor will affect the adjacent power system. The present invention replaces the aforementioned transformer with an AC-DC flyback converter, which does not charge the capacitor as much as a transformer, but is still adequate for general needs. It reduces the size, weight, and power requirements and losses of the entire system. At the same time, this fly-back converter uses current control mode (current m〇de control), which charges the capacitor in a wave-by-wave manner, which will suppress the generation of the glitch. A typical electric discharge pulse magnetization system circuit is shown in the first figure. The excitation action is to generate a magnetic field by winding a coil on the yoke and magnetize the material in the yoke. This part is called a magnetizing fixture, which is a load resistor on the circuit. RL) and series-connected coil assembly (L1) are used to describe its operation in three stages: 1. Capacitor (C2) charging phase: When scri is turned on, capacitor (C2) is first rectified via rectifier circuit (41) The DC is charged, and its polarity is as shown in the first figure 1355795. This process takes about several seconds. When the charging is completed, SCR1 is turned off. 2. Magnetization phase: At this stage, SCR2 must be triggered to be turned on, so it is stored in the capacitor (C2). The energy will be converted to the load resistance (RL) - coil assembly (L1). The load is also the magnetization facility, which magnetizes the material in the yoke. At this time, the recovery diode (D3) is non-conducting, when the inductor current reaches the maximum value. This phase ends when the reduction begins. 3. Inductor discharge phase: When the inductor current begins to decrease, the inductor voltage reverses, causing the recovery diode (D3) to begin to conduct, and the recovery diode (D3) is turned on. The capacitor voltage drops to zero and SCR2 is turned off. At this stage, the inductance energy of the coil component (L1) is consumed above the load resistance (RL) until the current drops to zero. The above-mentioned conventional magnetizers have the following defects in implementation: (1) During the charging phase of the capacitor, due to the near short circuit of the capacitor, it will cause current surge on the primary side of the transformer to affect the surrounding electrical equipment. At the same time, the capacity of the transformer and the rectifier diode must be quite large to avoid burning. The on-time current is large, so the current limiting resistor (R2) is required, and the efficiency is low, the cost is high, and the isolation transformer has a large rated capacity, and the output voltage thereof is about several thousand volts. Therefore, the conventional structure must use the volume. Large and heavy weight isolation transformer (3) Because the SCR is triggered by the phase angle (the trigger current is up to about several amps), a large amount of high harmonics are generated when the output voltage is controlled, thus making 1355795 electromagnetic interference. (4) In addition, A large number of harmonics are easier to inject into the power system, which in turn affects the power quality of users in adjacent areas, and the magnetic field formed by high harmonic currents - For synchronous or induction motors or magnetizers, not only can the real-value torque Torque, that is, the torque or the driving force, be provided, but the reverse torque will be reversed, which will reduce the mechanical operation efficiency of the motor or magnetizer; Adding transformer iron loss (eddy current loss and magnetic hysteresis loss) and copper loss, causing abnormal temperature rise or resonance of the core and winding, and noise noise and other noises. References: (1) Ravell, GH," An Over.view of Magnet Process" .Electrical Electronics Insulation Conference, 1 995, and Electrical Manufacturing & Coil Winding Conference. Proceeding, Sep., 1 995.
(2) Pill-Soo Kim and Yong Kim, “Part I Circuit, Thermal and Cost Modeling of Impuse Magnetizer” , IEEE 1999 Internal Conference on Power Electronics and Driver Systems,. PEDS' 99, July, Hong Kong, pp. 371-376. (3) Pi 11-Soo Kim, et al," An investigation of General Characteristics Impulse of Magnetizer(Π )-Field Modeling and Thermal Modeling of Magnetizing Fixture” , Proceedings of the industry application Society Annual Meeting 1999(IAS Annual Meeting **99), pp-1715-1721, USA, 1999. (4) Pill-Soo Kim, Field and thermal modeling for impulse Magnetizing fixture based on exact parameter estimation” Industrial Electronics,2001 Proceedings IS1E 2001.Proceedings.2001.IEEE International Symposium on,pp531-536 vol. 1,2001. (5) Mohan,et, al," Powerelectronics:converters,application ,and design" , John Wi1ey&Sons,1999. (6) Uni trode Corporation,” application handbook” Uni trode Corporation,1997. (7) Shen-yaur Chen; Kunsong Huang; Fuhshang Juang;，” Improvement of a capacitor discharge impulse magnetizer circuit” IEEE Power 8 1355795(2) Pill-Soo Kim and Yong Kim, “Part I Circuit, Thermal and Cost Modeling of Impuse Magnetizer”, IEEE 1999 Internal Conference on Power Electronics and Driver Systems,. PEDS' 99, July, Hong Kong, pp. 371- 376. (3) Pi 11-Soo Kim, et al, " An investigation of General Characteristics Impulse of Magnetizer (Π)-Field Modeling and Thermal Modeling of Magnetizing Fixture" , Proceedings of the industry application Society Annual Meeting 1999 (IAS Annual Meeting **99), pp-1715-1721, USA, 1999. (4) Pill-Soo Kim, Field and thermal modeling for impulse Magnetizing fixture based on exact parameter estimation" Industrial Electronics, 2001 Proceedings IS1E 2001. Proceedings. 2001. IEEE International Symposium on, pp 531-536 vol. 1, 2001. (5) Mohan, et, al, " Powerelectronics: converters, application, and design" , John Wi1ey & Sons, 1999. (6) Uni trode Corporation," Application handbook” Uni trode Corporation, 1997. (7) Shen-yaur Chen; Kunsong Huang; Fuhshang Juang;,” Improvement o f a capacitor discharge impulse magnetizer circuit" IEEE Power 8 1355795
Eiectronics_and Drive Systems. 2003. PEPS 2003. The Fifth Internet| Conference on Volume 2, 17-20 Nov. 2003 Page(s):1162 - 1163 Vol.2 有鑑於上述各種習用技術的缺失，本發明人等乃積 極努力研發，在經過不斷地努力研發及試驗下，終於有 • 本發明的研發成果產出。 • 【發明内容】 本發明之主要目的，在於提供一種包括有以切換式 _電源之驰返式轉換器作為充電裝置之磁化機，且採用峰 值電流模式控制馳返式轉换器（Peak Current M〇de Control Flyback Converter)作為電容充電方法，並以 pulse-by-pulse方法對電容充電，而可限制最大電流及 降低電源的諧波和瞬時電流，因為作動在高頻所以隔離 變壓器較輕，加上所需零件少，因而具有大幅降低成本、 鲁電源轉換效率佳以及降低機器重量與體積等特點。 本發明為達成上述功效所採用的技術手段在於，其 係以該磁化機之一線圈組件與該充電裝置電連接，用以 •使該線圈組件與一磁性組件互感產生一磁力而對一待磁 ，化件進行磁化作用，該充電裝置包括一整流電路、一馳 返式轉換H、-電流控制模組及_控制元件，並由該變 壓器之一初級繞組與該整流電路形成一電源輸入迴路， 以將該電源感應傳遞至該次級繞組中，且該電源輸入迴 1355795 路串設一開關元件，再由該變壓器之一次級繞組與該整 流濾波電路形成一可供輸出直流電源的電源輸出迴路， 該電流控制模組分別與該開關元件之一觸發部及該電源 •輸入迴路電連接，用以偵測流經該電源輸入迴路之一輸 .入電流及一輸出電壓以做為調變一脈波寬度的依據，使 遠觸發部得以該脈波來控制該開關元件的導通與戴止時 #間，以調節該輸入電流的大小，再以一控制元件控制該 電源輸出迴路與該線圈組件之間的電源通路者。 【實施方式】 壹.本發明之基本技術特徵 請參看第二、三圖所示，本發明主要係將切換式電 源架構運用於磁化機（1 〇)上，使切換式電源得以輸往磁 籲化機（10)的線圈組件（1〇中，為達上述功效，其係以該 磁化機（10)之一線圈組件（11)與該充電裝置（2〇)電連 接，用以使該線圈組件（11)與一磁性組件（12)互感產生 * 一磁力而對一待磁化件（圖中未示）產生磁化作用，其 - 中，該充電裝置（20)包括： 一整流電路（21),其包含二個與一交流電源電連接 的輸入部（210) ’及二個用以輸出脈動直流之電源的輸出 部（211)，在本圖不例中，該整流電路（21)係為一橋式整 1355795 流電路； 一驰返式轉換器（22)，其包含： 一變壓器（T1)，其包含一初級繞組（220)及一次級 繞組（221)’該初級繞組（220)二端分別與該整流電路（21) • 之其一該輸出部（211)及另一該輸出部（211)電連接，用 以形成一電源輸入迴路’而可將該電源感應傳遞至該次 鲁級繞組（221)中； 一串聯於該電源輸入迴路上的開關元件（23)，其包 含一用以控制該電源輸入迴路通、斷的觸發部（23〇)，在 本圖示例中，該開關元件（23)係選自電晶體以及m〇SFET 電晶體之其中一種；及 一整流遽波電路（2 4 )，其包含一用以整流的二極體 鲁 （D1)及一用以濾波及儲能的電容器（C1)，該二極體（D1) 一端與該次級繞組（2 21) —端電連接，該二極體（j) 1)另端 與該電容器（C1)之一端電連接，該電容器（C1)另端與該 * 次級繞組（221)另端電連接，用以形成一可供輸出直流電 ， 源的電源輸出迴路； 一電流控制模組（25)，其分別與該開關元件（23)之 該觸發部（230)及該電源輸入迴路電連接，用以偵測流經 該電源輸入迴路之一輸入電流及一輸出電壓以做為調變 1355795 一脈波寬度的依據，使該觸發 货。丨U30)得以該脈波來控 該開關元件（23)的導通與截止時 的大… 調即该輸入電流 控制兀件（30)，其串聯於該電源輸出迴路之負载 端’用以控制該電源輸出迴路與該線圈組件⑴）之間的 導通。 • 貳.驰返式轉換器之具體實施 2. 1驰返式轉換器之運作 本發明之馳返式轉換（22)器主要係運用在功率i〇〇w 以下輸出的電源供給上，由於該變壓器（τι)兼具輸出及 儲能電感作用’因而具有構件較為精簡及成本較為低廉 等諸多優點，因此，於電源轉換器之應用上日益受到重 視。 請參看第二、三圖所示，當開關元件（23)切入時， 使该電源輸入迴路得以導通，該二極體（D1)則截止，此 -時，5亥電源經該初級繞組（2 2 0 )儲存在該變壓器（τ 1)中， ’並由5亥電谷器（C1)放電以供應電源輸出迴路負載端的直 流電源，使該線圈組件（丨丨）得以獲得較佳化之穩壓效果 的電源供給，而不受負載電流變化影響磁化機（1 〇)的運 轉。 12 明 5795 €開關元件（23)開路時，使電源輸入迴路截止該 二極體（D1)則導通，此時，即可將儲存在該變壓器（τι) 中之該電源由該次級繞組（221)對該電容器（C1)充電，同 時供應電源輸出迴路負载端的直流電源，使該線圈組件 (11)得以獲得較佳化之穩壓效果的電源供給。 2. 2開關元件之具體實施 春 咕參看第一、二圖所示，該開關元件（2 3 )係選自電 ㈤體以及MOSFET電晶體之其中一種。該開關元件(23)係 為一電晶體，該電晶體包含有一作為該觸發部（23〇)的基 極，及分別串聯在該電源輸入迴路上的一射極及一集 極’而可藉由該基極的觸發來控制該電源輪人迴路的通 或斷。 • 請參看第二圖所示，上述具體實施例中，該電晶體 之集極與該電源輸入迴路之間電連接有一用以感測該輸 入電流的感測電阻（R1)。 參·電流控制模組之具體實施 3. 1功率因素調整電路之具體實施 人明參看第二、三圖所示，該電流控制模組（25)更包 含-功率因素調整電路（250)，用以調整所輸出之該直流 電源的功率因素。 13 1355795 3. 2脈波調變控制電路pWM之具體實施 睛參看第二、三圖所示，其令，為達調變脈波寬度， 以求輸出電壓穩定之目的，本發明於一種具體實施例， 係採用PWM模式，並採取輸出電壓以及另一電流訊號作 為回授之狀態變數作為電流模式控制，電流取自電晶體 開關電流’因而本發明之該電流控制模組（25)更包含： 一脈波調變控制電路PWM(251)，其與該開關元件（23) 之該觸發部（230)電連接’其可依據所偵測該輸入電流及 該輸出電壓來調變該脈波之寬度；及 一與該脈波調變控制電路？^^(251)電連接的驅動電 路（252)，其受該脈波調變控制電路pwM(251)之控制來驅 動該開關元件（23)的啟、閉，並藉由該開關元件（23)的 啟閉’使该初級繞組（2 2 〇)之該電源傳遞給該次級繞組 (221) 〇 請參看第三、四圖所示，上述具體實施例中，該電 流控制模組（25)更包含一回授控制電路（253)，其先將位 於該電源輸出迴路上之輸出電壓與基準電壓比較，再將 该輸出電壓與一基準電壓之誤差值經一誤差放大器（254) 處理後得到一控制電壓，再將該控制電壓與該輸入電流 所轉換的電壓訊號經一比較器（255)進行比較而可產生 1355795 一比較訊號，並且將該比較訊號傳送至一脈波調變控制 電路PWM(251)中，使該脈波調變控制電路pwM(251)調變 輸往該開關元件（23)之該觸發部（230)的該脈波寬度，藉 由調變該脈波寬度來控制該開關元件（23)之導通與截止 時間’以限制該輸入電流的大小。 肆·控制元件之具體實施 請參看第二、四圖所示，該控制元件（3〇)為一石夕控 整流器SCR，並於該電源輸出迴路位於該矽控整流器SCR 之後端並聯有一反向的二極體（D2)，以作為線圈組件（丨j) 放電階段時的導通回復之用。 請參看第二、四圖所示，當該矽控整流器SCR被觸發 導通後即進入磁化機之磁化階段，於是儲存於電容器（Ci)之 能量轉換至線圈組件（11)及RL中，藉以磁化待磁化件。此時， 二極體（D2)不導通，當線圈組件（11)之電感電流到達最大值 後開始減少時這階段就結束。 當線圈組件（11)之電感電流開始減小時，線圈組件（11) 之電壓反向使得二極體（D2)開始導通，而二極體（D2)導通後， 電容器（C1)電壓降為零而該矽控整流器s c R關閉。此階段線圈 組件（11)之電感能量消耗在RL上面，一直到電流降為零為止。 伍·結論 15 1355795 因此，藉由馳返式轉換器的設置，使本發明確實可 以作為磁化機的充電裝置，且採用以以Current Control Flyback C〇nverte作為電容充電方法，並以 PHPulse方法對電容充電’進而限制最大電流及 降低電源的諧波和瞬時電流，因為作動在高頻所以隔離 變壓器較輕，加上所需零件少，因而具有大幅降低成本、 電源轉換效率佳以及降低機器重量與體積等特點。 以上所述，僅為本發明之一可行實施例，並非用以 限定本發明之專利範圍，凡舉依據下列中請專利範圍所 述之内I、特徵以及其精神而為之其他變化的等效實 施，皆應包含於本發明之專利範圍内。本發明所具體界 定於申請專利範圍之結構特徵’未見於同類物品且具 實用性與進步性’ 6符合發明專利要件，爰依法具文提 出申凊’謹請制依法核予專利，以維護本申請人合 法之權益。 【圖式簡單說明】 第一圖係習用充電裝置之電路示意圖。 第二圖係本發明基本架構之示意圖。 第三圖係本發明充電裝置之電路示意圖。 第四圖係本發明充電裝置之詳細電路示意圖 1355795 【主要元件符號說明】 (AC)交流電源 (11)(L1)線圈組件 * (20)(40)充電裝置 -(210)輸入部 (22) 驰返式轉換器 Φ (220)初級繞組 (23) 開關元件 (R1)感測電阻 (RL)負載電阻 (D1)(D2)二極體 (C1)(C2)電容器 I (250)功率因素調整電路 PWM(252)驅動電路 (254)誤差放大器 .(30)控制元件 (10)磁化機 (12)磁性組件 (21)(41)整流電路 (211)輸出部 (T1)(T2)變壓器 (2 21)次級繞組 (230)觸發部 (R2)限流電阻 (24) 整流濾波電路 (D3)恢復二極體 (25) 電流控制模組 (251)脈波調變控制電路 (253)回授控制電路 (255)比較器 17 .Eiectronics_and Drive Systems. 2003. PEPS 2003. The Fifth Internet|Conference on Volume 2, 17-20 Nov. 2003 Page(s): 1162 - 1163 Vol.2 In view of the above-mentioned various conventional technologies, the inventors are active. Efforts to develop, and after continuous efforts to develop and test, finally have the research and development results of the invention. SUMMARY OF THE INVENTION A main object of the present invention is to provide a magnetizer including a switching-type power supply-type return converter as a charging device, and a peak current mode control flyback converter (Peak Current M〇) De Control Flyback Converter) as a capacitor charging method, and charging the capacitor with pulse-by-pulse method, which can limit the maximum current and reduce the harmonic and instantaneous current of the power supply, because the isolation transformer is light at high frequency, plus Less parts are required, resulting in significant cost reduction, good power conversion efficiency, and reduced weight and volume. The technical means for achieving the above-mentioned effects is that the coil component of the magnetizer is electrically connected to the charging device for causing the coil component and a magnetic component to mutually generate a magnetic force and to be magnetized. The device is magnetized, and the charging device comprises a rectifying circuit, a flyback conversion H, a current control module and a _ control element, and a primary input of the transformer forms a power input circuit with the rectifying circuit. The power source is inductively transmitted to the secondary winding, and the power input is back to the 1355795 circuit to set a switching component, and then a secondary winding of the transformer and the rectifying and filtering circuit form a power output circuit for outputting a DC power supply. The current control module is electrically connected to the triggering portion of the switching element and the power supply input circuit for detecting an input current and an output voltage flowing through the power input circuit as a modulation one. The basis of the pulse width is such that the far-trigger portion can control the conduction between the switching element and the wear-stop time by the pulse wave to adjust the magnitude of the input current. In a control element between the power supply passage by the power output circuit and the coil assembly. [Embodiment] 基本. The basic technical features of the present invention are shown in the second and third figures. The present invention mainly applies a switched power supply architecture to a magnetizer (1 〇), so that the switched power supply can be exported to the magnetic The coil assembly (1) of the chemical machine (10) is electrically connected to the charging device (2〇) by a coil assembly (11) of the magnetizer (10) for making the coil The component (11) interacts with a magnetic component (12) to generate a magnetism to magnetize a magnet to be magnetized (not shown), wherein the charging device (20) comprises: a rectifier circuit (21) The utility model comprises two input parts (210)' electrically connected to an alternating current power source and two output parts (211) for outputting a power source of the pulsating direct current. In the example of the figure, the rectifying circuit (21) is A bridge-type 1559795 current circuit; a fly-back converter (22), comprising: a transformer (T1) comprising a primary winding (220) and a primary winding (221) 'the primary winding (220) two ends And the output unit (211) and the other of the rectifier circuit (21) The part (211) is electrically connected to form a power input circuit 'to transmit the power source into the secondary winding (221); a switching element (23) connected in series to the power input circuit, comprising a triggering portion (23〇) for controlling the power input loop to be turned on and off. In the example of the figure, the switching element (23) is selected from one of a transistor and a m〇SFET transistor; and a rectification The chopper circuit (24) includes a diode (D1) for rectification and a capacitor (C1) for filtering and storing energy, one end of the diode (D1) and the secondary winding ( 2 21) - terminal electrical connection, the other end of the diode (j) 1) is electrically connected to one end of the capacitor (C1), and the other end of the capacitor (C1) is electrically connected to the other end of the * secondary winding (221) a current output circuit for outputting a direct current, source; a current control module (25) electrically connected to the triggering portion (230) of the switching element (23) and the power input circuit, respectively To detect the input current and an output voltage flowing through one of the power input loops as a modulation 1357795 According to the pulse width, so that the trigger goods.丨U30) is capable of controlling the on and off of the switching element (23) by the pulse wave. The input current control element (30) is connected in series to the load end of the power output circuit to control the The conduction between the power output loop and the coil assembly (1)). • 贰. The implementation of the flyback converter 2. The operation of the flyback converter The reversing converter (22) of the present invention is mainly used for the power supply of the output below the power i〇〇w, since The transformer (τι) combines the advantages of output and energy storage inductance, which has the advantages of relatively simple components and low cost. Therefore, it has received increasing attention in the application of power converters. Please refer to the second and third figures. When the switching element (23) is cut in, the power input circuit is turned on, and the diode (D1) is turned off. At this time, the 5 hai power supply passes through the primary winding (2). 2 0 ) stored in the transformer (τ 1), 'and discharged by the 5 hp grid (C1) to supply the DC power supply at the load end of the power supply output loop, so that the coil assembly (丨丨) can be better stabilized The effect of the power supply is not affected by the change of the load current affecting the operation of the magnetizer (1 〇). 12 Ming 5795: When the switching element (23) is open, the power input circuit is turned off and the diode (D1) is turned on. At this time, the power stored in the transformer (τι) can be used by the secondary winding ( 221) charging the capacitor (C1) while supplying a DC power source at the load end of the power output loop, so that the coil assembly (11) can obtain a power supply with a better voltage stabilizing effect. 2. 2 Switching element implementation Spring 咕 See the first and second figures, the switching element (23) is selected from one of the electric (five) body and the MOSFET transistor. The switching element (23) is a transistor, and the transistor includes a base as the triggering portion (23〇), and an emitter and a collector respectively connected in series to the power input circuit. The on/off of the power wheel human circuit is controlled by the trigger of the base. • Referring to the second embodiment, in the above embodiment, a sensing resistor (R1) for sensing the input current is electrically connected between the collector of the transistor and the power input circuit. The specific implementation of the current control module is as follows: 1. The current control module (25) further includes a power factor adjustment circuit (250), as shown in the second and third figures. To adjust the power factor of the DC power source output. 13 1355795 3. The specific implementation of the 2 pulse wave modulation control circuit pWM is shown in the second and third figures, so that the purpose of the modulation pulse width is to achieve stable output voltage, the present invention is embodied in a specific implementation. For example, the PWM mode is adopted, and the output voltage and another current signal are used as the feedback state variable as the current mode control, and the current is taken from the transistor switch current. Thus, the current control module (25) of the present invention further comprises: a pulse modulation control circuit PWM (251) electrically coupled to the triggering portion (230) of the switching element (23) for modulating the pulse wave according to the detected input current and the output voltage Width; and one with the pulse wave modulation control circuit? ^^(251) an electrically connected driving circuit (252) controlled by the pulse wave modulation control circuit pwM (251) to drive the switching element (23) to be turned on and off, and by the switching element (23) The opening and closing 'transfers the power of the primary winding (2 2 〇) to the secondary winding (221). Referring to Figures 3 and 4, in the above embodiment, the current control module (25) The method further includes a feedback control circuit (253), which first compares the output voltage on the power output loop with the reference voltage, and then processes the error value of the output voltage and a reference voltage through an error amplifier (254). Obtaining a control voltage, and comparing the control voltage with the voltage signal converted by the input current through a comparator (255) to generate a 1355795-compare signal, and transmitting the comparison signal to a pulse-wave modulation control circuit In the PWM (251), the pulse wave modulation control circuit pwM (251) is modulated to transmit the pulse width of the pulse portion to the trigger portion (230) of the switching element (23) by modulating the pulse width. Controlling the on and off time of the switching element (23) to limit The size of this input current. For the specific implementation of the control element, please refer to the second and fourth figures. The control element (3〇) is a rock-controlled rectifier SCR, and there is a reverse connection in parallel with the power output loop of the control rectifier SCR. The diode (D2) serves as a turn-on recovery for the coil assembly (丨j) during the discharge phase. Referring to the second and fourth figures, when the SCR is triggered to conduct, it enters the magnetization phase of the magnetizer, and the energy stored in the capacitor (Ci) is converted into the coil assembly (11) and the RL, thereby magnetizing. To be magnetized. At this time, the diode (D2) is not turned on, and the phase ends when the inductance current of the coil component (11) starts to decrease after reaching the maximum value. When the inductor current of the coil component (11) begins to decrease, the voltage of the coil component (11) is reversed so that the diode (D2) starts to conduct, and after the diode (D2) is turned on, the capacitor (C1) voltage drops to zero. The pilot rectifier sc R is turned off. At this stage, the inductive energy of the coil assembly (11) is consumed above the RL until the current drops to zero. Wu. Conclusion 15 1355795 Therefore, with the setting of the flyback converter, the present invention can be used as a charging device for a magnetizer, and a Current Control Flyback C〇nverte is used as a capacitor charging method, and a capacitor is used in a PHPulse method. Charging' in turn limits the maximum current and reduces the harmonics and instantaneous current of the power supply. Because the operating transformer is light at high frequencies, the isolation transformer is lighter, and fewer parts are required, thus significantly reducing cost, power conversion efficiency, and reducing machine weight and volume. Features. The above description is only one of the possible embodiments of the present invention, and is not intended to limit the scope of the patents of the present invention, and the equivalents of other changes in accordance with the I, the features and the spirit thereof as set forth in the following patent claims. Implementations are intended to be included in the scope of the invention. The structural features of the invention specifically defined in the scope of the patent application are not found in the same kind of articles and have practicality and progress. 6 Comply with the requirements of the invention patents, and apply for the law according to law, and please legally approve the patents to maintain the The legal rights of the applicant. [Simple description of the drawing] The first figure is a schematic circuit diagram of a conventional charging device. The second figure is a schematic diagram of the basic structure of the present invention. The third figure is a schematic circuit diagram of the charging device of the present invention. 4 is a detailed circuit diagram of the charging device of the present invention 1355795 [Explanation of main component symbols] (AC) AC power supply (11) (L1) coil assembly * (20) (40) Charging device - (210) Input portion (22) Swive-back converter Φ (220) Primary winding (23) Switching element (R1) Sense resistance (RL) Load resistance (D1) (D2) Diode (C1) (C2) Capacitor I (250) Power factor adjustment Circuit PWM (252) drive circuit (254) error amplifier. (30) Control element (10) Magnetizer (12) Magnetic component (21) (41) Rectifier circuit (211) Output (T1) (T2) Transformer (2 21) Secondary winding (230) Trigger (R2) Current limiting resistor (24) Rectifier filter circuit (D3) Recovery diode (25) Current control module (251) Pulse modulation control circuit (253) Control circuit (255) comparator 17 .