TWI711263B - Inductive load drive circuit - Google Patents

Inductive load drive circuit Download PDF

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TWI711263B
TWI711263B TW106130269A TW106130269A TWI711263B TW I711263 B TWI711263 B TW I711263B TW 106130269 A TW106130269 A TW 106130269A TW 106130269 A TW106130269 A TW 106130269A TW I711263 B TWI711263 B TW I711263B
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recovery
inductive load
current
circuit
coil
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TW106130269A
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Chinese (zh)
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TW201830843A (en
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永野卓
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日商油研工業股份有限公司
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    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • FMECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F16ENGINEERING ELEMENTS AND UNITS; GENERAL MEASURES FOR PRODUCING AND MAINTAINING EFFECTIVE FUNCTIONING OF MACHINES OR INSTALLATIONS; THERMAL INSULATION IN GENERAL
    • F16KVALVES; TAPS; COCKS; ACTUATING-FLOATS; DEVICES FOR VENTING OR AERATING
    • F16K31/00Actuating devices; Operating means; Releasing devices
    • F16K31/02Actuating devices; Operating means; Releasing devices electric; magnetic
    • F16K31/06Actuating devices; Operating means; Releasing devices electric; magnetic using a magnet, e.g. diaphragm valves, cutting off by means of a liquid
    • F16K31/0675Electromagnet aspects, e.g. electric supply therefor
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00Details of apparatus for conversion
    • H02M1/32Means for protecting converters other than automatic disconnection
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00Conversion of dc power input into dc power output
    • H02M3/22Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00Details of apparatus for conversion
    • H02M1/0003Details of control, feedback or regulation circuits
    • H02M1/0038Circuits or arrangements for suppressing, e.g. by masking incorrect turn-on or turn-off signals, e.g. due to current spikes in current mode control

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • General Engineering & Computer Science (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Mechanical Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

[課題] 提供一種不會發生發熱,可在感應負載停止時的電流減少實現高響應性,且可進行比以往更高響應且有效率的電流控制的感應負載驅動電路。   [解決手段] 在具有切換電源電路的感應負載驅動電路中,以在感應負載的電流減少時,一邊使該感應負載的反電動勢發生一邊回收的能量回收電路而言,形成為包含:在同一鐵心具有以串聯且彼此相反極性連接在感應負載之電阻值不同的二個一次側線圈、及連接在切換變壓器的一次側的一個二次側線圈的回收用變壓器;及與二個一次側線圈之中相對電阻值小的小電阻一次側線圈串聯配置而按照根據來自控制電路的回收指令訊號之藉由第2脈衝訊號發生裝置所得之脈衝訊號進行動作,來控制流至小電阻一次側線圈的電流的回收控制元件者,控制電路係在感應負載的電流減少時使藉由相對回收控制元件之第2脈衝訊號發生裝置所得之脈衝訊號的脈衝寬度調整,將回收控制元件進行OFF控制一定時間,藉此一邊使感應負載的反電動勢發生一邊對回收用變壓器的相對電阻值大的大電阻一次側線圈流通電流,藉此使鐵芯磁通量改變而使能量傳達至相對應的二次側線圈者。[Question] To provide an inductive load drive circuit that does not generate heat, can reduce the current when the inductive load stops, realizes high responsiveness, and can perform current control with higher response and efficiency than before. [Solution] In an inductive load drive circuit with a switching power supply circuit, when the current of the inductive load decreases, the energy recovery circuit that generates the back electromotive force of the inductive load while recovering is formed to include: A recovery transformer having two primary coils connected in series and opposite polarity to the inductive load with different resistance values, and a secondary coil connected to the primary side of the switching transformer; and among the two primary coils The relatively small resistance primary side coil is arranged in series and operates according to the pulse signal obtained by the second pulse signal generator according to the recovery command signal from the control circuit to control the current flowing to the small resistance primary side coil For the recovery control element, the control circuit adjusts the pulse width of the pulse signal obtained by the second pulse signal generating device relative to the recovery control element when the current of the inductive load decreases, and the recovery control element is turned off for a certain period of time, thereby While generating the back electromotive force of the inductive load, a current flows through the large-resistance primary coil of the recovery transformer with a large relative resistance value, thereby changing the magnetic flux of the iron core to transfer energy to the corresponding secondary coil.

Description

感應負載驅動電路Inductive load drive circuit

[0001] 本發明係關於用以使例如電磁線圈(solenoid)或馬達等感應負載驅動的電路,詳言之係關於在藉由PWM控制方式所得之切換電源的電路構成組合能量回收電路來進行電流控制的感應負載驅動電路者。[0001] The present invention relates to a circuit used to drive an inductive load such as a solenoid (solenoid) or a motor, and more specifically, it relates to a combined energy recovery circuit that forms a switching power supply circuit obtained by a PWM control method to conduct current Controlled inductive load drive circuit.

[0002] 馬達或電磁線圈等具有線圈成分且將電能透過電磁力而轉換成機械式運動的感應負載係作為致動器而被利用在各種裝置。在感應負載的驅動控制方式大致區分有:脈衝寬度調變,所謂PWM(pulse width modulation)控制與比例控制。前者係當將負荷進行ON/OFF控制時,使脈衝寬度的負載比(duty ratio),亦即ON/OFF比率對應輸入訊號的大小而改變者,後者係藉由使與負荷作串聯連接的控制元件的兩端電壓為可變而使其損失來進行控制者。   [0003] 以PWM方式而言,例如有使用專利文獻1所見之切換電源的電路構成,藉由將商用的高交流電壓形成為低直流電壓而安定地供給至感應負載的驅動電路,進行電流控制者。   [0004] 具體而言,如圖5(a)中顯示基本構成,為一種使用切換電源電路的感應負載驅動電路100,其係將來自供給電源112的交流先藉由橋式二極體113進行整流且另外以平滑電容器114予以平滑化的直流,根據指令訊號121,藉由切換由FET(Field Effect Transistor:場效電晶體)等半導體元件所成之切換元件115而轉換成脈衝波的交流之後,送入至切換變壓器116,且將交流電壓進行降壓轉換成預定的交流電壓。   [0005] 若在該感應負載驅動電路100進行電流控制,當在切換變壓器116的一次側將輸入側直流進行交流轉換時,在控制電路中根據指令訊號121,以成為預定的脈衝波寬(切換的ON/OFF循環的ON時間)的方式,例如由PWM控制器(PWM-IC)等脈衝訊號發生裝置124發生脈衝訊號。接著,可藉由根據利用指令訊號與輸出側的電流感測器125所得之檢測結果的反饋控制,調整脈衝波寬來進行切換,因此即使電源及負荷變動,輸出電流亦保持為一定,可得安定化的直流。   [0006] 在該方式中,係以切換變壓器116,一次側的能量藉由使將切換元件115進行ON/OFF切換而形成為高頻交流的電流由一次側線圈Lp電磁感應至二次側線圈Ls而被傳達能量,但是因形成為高頻交流,變壓器本身小型即可,由於發熱少,因此成為高效率。如上所示被傳達的交流電流係在二次側的整流二極體117被整流而流入至感應負載111,但是在二極體被整流的感應電流係成為斷續波形,因此若直接流至感應負載,感應負載的兩端電壓會大幅變動。因此,為了將其平滑化,形成為在二次側配置平滑電容器118,且經平滑化的直流被輸出至感應負載111的構成。   [0007] 該二次側的平滑電容器118係容量愈小,電路響應愈為高速。相反地,以電容器無法完全平滑化而漣波電壓變大,因此電流控制的安定性會惡化。因此,將PWM周期更加高速化,電容器容量即使小,亦可吸收漣波電流,藉此可達成高響應化,但是感應負載電流OFF時的響應性係以下所示成為在構造上為遲緩者。   [0008] 亦即,將感應負載電流形成為OFF時,必須將切換變壓器一次側的切換元件115形成為OFF一定,停止對變壓器二次側的感應,使平滑電容器118完全放電。但是,若平滑電容器的容量相對負荷所發生的反電動勢為充分小時,若平滑電容器放電,如圖5(b)所示,感應負載的轉流電流101係在平滑電容器118反向充電的同時,轉流電流亦透過整流二極體而流至變壓器二次側線圈Ls。此時在一次側線圈Lp,若與感應負載的轉流時間相比較,為可忽略的程度的時間,但是感應電流102透過FET的內置二極體來流通。此外,變壓器二次側線圈的阻抗亦低,因此感應負載OFF時的轉流電流係幾乎透過整流二極體來流通。結果,響應性係與具有二極體轉流電路的驅動電路為等效,耗費響應時間。   [0009] 如上所示,在利用PWM方式的切換電源的電路構成的感應負載驅動電路中,雖然效率優,但是在響應性有問題,無法進行感應負載電流的減少速度的控制。相對於此,比例控制方式係藉由在控制元件的兩端將電壓進行可變調整而使其損失來進行控制者,因此有發熱的問題。 [先前技術文獻] [專利文獻]   [0010]   [專利文獻1] 日本特開2012-217238號公報   [專利文獻2] 日本特開平07-59397號公報[0002] Inductive loads such as motors and electromagnetic coils that have coil components and convert electrical energy into mechanical motion through electromagnetic force are used as actuators in various devices. The driving control methods of inductive loads are roughly divided into: pulse width modulation, so-called PWM (pulse width modulation) control and proportional control. The former is when the duty ratio of the pulse width (duty ratio), that is, the ON/OFF ratio is changed according to the magnitude of the input signal when the load is ON/OFF control, the latter is controlled by connecting the load in series The voltage at both ends of the element is variable and its loss is controlled. [0003] In the PWM method, for example, there is a circuit configuration using a switching power supply as seen in Patent Document 1. By forming a commercial high AC voltage into a low DC voltage and stably supplying the drive circuit to an inductive load, current control is performed By. [0004] Specifically, as shown in FIG. 5(a), the basic structure is shown as an inductive load driving circuit 100 using a switching power supply circuit. The AC from the power supply 112 is first performed by a bridge diode 113. The rectified and smoothed direct current with a smoothing capacitor 114 is converted into a pulsed alternating current by switching the switching element 115 made of a semiconductor element such as FET (Field Effect Transistor) according to the command signal 121 , Is sent to the switching transformer 116, and the AC voltage is stepped down and converted into a predetermined AC voltage. [0005] If current control is performed in the inductive load drive circuit 100, when the input side DC is converted to AC on the primary side of the switching transformer 116, the control circuit will use the command signal 121 to achieve a predetermined pulse width (switching For example, a pulse signal generating device 124 such as a PWM controller (PWM-IC) generates a pulse signal. Then, the pulse width can be adjusted to switch by feedback control based on the detection result obtained by the command signal and the current sensor 125 on the output side. Therefore, even if the power supply and load fluctuate, the output current remains constant. Stabilized DC. [0006] In this method, a switching transformer 116 is used, and the energy on the primary side is formed into a high-frequency alternating current by turning the switching element 115 ON/OFF, electromagnetically induced from the primary side coil Lp to the secondary side coil. Ls transfers energy, but because it is formed as a high-frequency alternating current, the transformer itself is small, and because it generates less heat, it becomes highly efficient. The AC current transmitted as shown above is rectified by the rectifier diode 117 on the secondary side and flows into the inductive load 111, but the induced current rectified by the diode becomes an intermittent waveform, so if it flows directly to the inductive load Load, the voltage across the inductive load will vary greatly. Therefore, in order to smooth it, a smoothing capacitor 118 is arranged on the secondary side, and the smoothed direct current is output to the inductive load 111.  [0007] The smaller the capacity of the smoothing capacitor 118 on the secondary side, the faster the circuit response. Conversely, since the capacitor cannot be smoothed completely and the ripple voltage becomes larger, the stability of the current control will deteriorate. Therefore, the PWM cycle is made faster, and even if the capacitor capacity is small, the ripple current can be absorbed, thereby achieving high response. However, the response when the inductive load current is OFF is structurally slow as shown below.  [0008] That is, when the inductive load current is turned off, the switching element 115 on the primary side of the switching transformer must be turned off constant, stop the induction on the secondary side of the transformer, and discharge the smoothing capacitor 118 completely. However, if the capacity of the smoothing capacitor is sufficiently small relative to the back electromotive force generated by the load, if the smoothing capacitor is discharged, as shown in Figure 5(b), the shunt current 101 of the inductive load is at the same time that the smoothing capacitor 118 is reversely charged. The shunt current also flows through the rectifier diode to the secondary winding Ls of the transformer. At this time, in the primary coil Lp, compared with the commutation time of the inductive load, it is a negligible time, but the induced current 102 flows through the built-in diode of the FET. In addition, the impedance of the secondary winding of the transformer is also low, so the commutation current when the inductive load is OFF almost flows through the rectifier diode. As a result, the responsiveness is equivalent to a driving circuit with a diode commutation circuit, which consumes response time.  [0009] As described above, in the inductive load drive circuit configured with a circuit for switching the power supply of the PWM method, although the efficiency is excellent, there is a problem with the responsiveness, and it is impossible to control the reduction speed of the inductive load current. On the other hand, the proportional control method is to control the voltage by variably adjusting the voltage at both ends of the control element to lose it, and therefore there is a problem of heat generation. [Prior Art Document] [Patent Document]   [0010]   [Patent Document 1] Japanese Patent Laid-Open No. 2012-217238   [Patent Document 2] Japanese Patent Laid-Open No. 07-59397

(發明所欲解決之課題)   [0011] 另一方面,若為電力為100W以下之輸出小的一般電磁線圈等,蓄積在負荷的能量因發熱而被消耗,但是所消耗的能量少至數瓦特,因此作為進行電力回收的成本效益,並不適當,因此並不進行能量的回收。此在馬達驅動裝置中亦同,在低輸出的系統中,回生能量因發熱而被消耗。在無大電力的電磁線圈的現況下,不必須進行能量回收,因此具有供其之用的機構的驅動電路在實質上亦未被建構。   [0012] 但是,若為驅動電壓必須要有一般使用的DC48V以上的電源的負荷時,負荷電力變大,減少感應負載的電流時,係發生突波電壓,該能量會因發熱而消耗,因此有白費的情形。此外,任何驅動方式均必須要有AC-DC電源或DC-DC(升壓)電源,電路規模變大。   [0013] 其中,例如,如專利文獻2所示,在感應負載驅動裝置中,亦有具備有回收轉流能量的手段者,俾以在感應負載停止時可確保負荷電流良好降低。在專利文獻2中,係形成為在感應負載非驅動時,在使負荷電流回流的回流路配置變壓器的二次側繞組,設置將二次側繞組或一次側繞組短路的開關手段,在感應負載停止時,將該開關手段形成為OFF者。藉此,在二次側繞組以使負荷電流收歛的方向發生高壓,降低負荷電流,將在變壓器的一次側發生電流而蓄積在感應負載的能量在電源回生。   [0014] 但是,即使當將感應負載進行OFF時將電流流至變壓器二次側,該電壓變化亦僅為1次,因此無法有效地使能量恢復至一次側。即使將並聯連接在二次側繞組的開關手段進行ON/OFF,變壓器繞組的電流電路亦未被遮斷,因此並無法將二次側變壓器的線圈電流瞬時遮斷,感應負載的能量消耗不充分,因此感應負載的響應性不充分。   [0015] 本發明之目的係鑑於上述問題點,提供一種即使在感應負載為大型的情形下,亦不會有發生發熱的情形,而可在感應負載停止時的電流減少實現高響應性,可進行比以往更高響應且有效率的電流控制的感應負載驅動電路。 (解決課題之手段)   [0016] 為達成上述目的,請求項1所記載之發明之感應負載驅動電路係具有:切換電源電路、及控制電路,   該切換電源電路係具備有:將來自電源的交流進行整流的整流橋式二極體;將經整流的直流平滑化的一次側平滑電容器;將藉由前述一次側平滑電容器被平滑化的直流,藉由以根據來自脈衝訊號發生手段的脈衝訊號的周期的切換元件的ON/OFF切換,被轉換成脈衝波的交流者,變壓成預先設定的交流電壓而傳達至二次側的切換變壓器;將被傳達至二次側的交流進行整流的二次側二極體;及將經整流的直流更加平滑化而進行輸出的二次側平滑電容器,   該控制電路係根據指令訊號與前述切換電源電路的輸出側的檢測結果,調整藉由前述脈衝訊號發生裝置所得之脈衝訊號的脈衝寬度,來控制前述切換元件的ON/OFF切換,   該感應負載驅動電路係:   另外具備有:能量回收電路,其係在前述感應負載的電流減少時,一邊使該感應負載的反電動勢發生一邊回收,   前述能量回收電路係包含:   在同一鐵心具有以串聯且彼此相反極性連接在前述感應負載之電阻值不同的二個一次側線圈、及連接在前述切換變壓器的一次側的一個二次側線圈的回收用變壓器;及   與前述二個一次側線圈之中相對電阻值小的小電阻一次側線圈串聯配置而按照根據來自前述控制電路的回收指令訊號之藉由第2脈衝訊號發生裝置所得之脈衝訊號進行動作,來控制流至前述小電阻一次側線圈的電流的回收控制元件,   前述控制電路係在前述感應負載的電流減少時使藉由相對前述回收控制元件之前述第2脈衝訊號發生裝置所得之脈衝訊號的脈衝寬度調整,將前述回收控制元件進行OFF控制一定時間,藉此一邊使前述感應負載的反電動勢發生一邊對前述回收用變壓器的相對電阻值大的大電阻一次側線圈流通電流,藉此使鐵芯磁通量改變而使能量傳達至相對應的二次側線圈者。   [0017] 請求項2所記載之發明之感應負載驅動電路係在請求項1所記載之感應負載驅動電路中,   另外具備有第2回收控制元件,其係與前述回收用變壓器的前述大電阻一次側線圈串聯配置,以將前述小電阻一次側線圈的前述回收控制元件呈OFF時的電壓成為一定的方式,限制流至前述大電阻一次側線圈的電流。 (發明之效果)   [0018] 藉由本發明之感應負載驅動電路,在切換電源電路構成另外具備有藉由一次側線圈與感應負載作串聯連接的回收用變壓器所得之能量回收電路,藉此可在與電源側絕緣之感應負載的電流減少時,一邊使該感應負載的反電動勢發生一邊良好地回收,因此既無發熱損失亦有效率地實現感應負載電流停止時的高響應。   尤其,形成為藉由以彼此相反極性的大電阻與小電阻的二個線圈構成能量回收電路的回收用變壓器的一次側,在定常狀態下,係無感應化,防止負荷電流增加時的電流上升速度的遲緩,同時透過予以PWM驅動控制的回收控制元件來控制小電阻一次側線圈的電流的構成,藉此,可高速控制感應負載停止時的負荷電流減少速度,因此具有可比以往更有效率的且高響應進行感應負載的電流控制的效果。(Problem to be solved by the invention)   [0011] On the other hand, if it is a general electromagnetic coil with a power of 100W or less and a small output, the energy stored in the load is consumed by heat, but the energy consumed is as little as a few watts Therefore, it is not appropriate as the cost-effectiveness of power recovery, so energy recovery is not performed. This is the same in motor drive devices. In low-output systems, the regenerative energy is consumed due to heat. In the current situation where there is no electromagnetic coil with large power, energy recovery is not necessary. Therefore, a drive circuit with a mechanism for it has not been constructed substantially. [0012] However, if a load of a generally used power supply of DC48V or higher is necessary for the driving voltage, the load power increases and when the current of the inductive load is reduced, a surge voltage occurs, and the energy is consumed by heat. There is a waste of money. In addition, any driving method must have an AC-DC power supply or a DC-DC (boost) power supply, and the circuit scale becomes larger.  [0013] Among them, for example, as shown in Patent Document 2, in the inductive load driving device, there are also those equipped with a means for recovering the commutation energy so as to ensure a good reduction in the load current when the inductive load stops. In Patent Document 2, when the inductive load is not driven, the secondary winding of the transformer is placed in the return path that returns the load current, and switching means is provided to short-circuit the secondary winding or the primary winding. When stopping, turn off the switch means. As a result, a high voltage is generated in the secondary winding in a direction in which the load current is converged, the load current is reduced, and the energy generated in the primary side of the transformer and stored in the inductive load is regenerated in the power supply.  [0014] However, even if the current flows to the secondary side of the transformer when the inductive load is turned off, the voltage change is only once, so energy cannot be effectively restored to the primary side. Even if the switching means connected in parallel to the secondary winding is turned on/off, the current circuit of the transformer winding is not interrupted. Therefore, the coil current of the secondary transformer cannot be interrupted instantaneously, and the energy consumption of the inductive load is insufficient , So the responsiveness of the inductive load is insufficient. [0015] In view of the above-mentioned problems, the purpose of the present invention is to provide a method that does not generate heat even when the inductive load is large, and can reduce the current when the inductive load is stopped to achieve high responsiveness. An inductive load drive circuit with higher response and more efficient current control than before. (Means for Solving the Problem)   [0016] In order to achieve the above object, the inductive load drive circuit of the invention described in claim 1 has: a switching power supply circuit and a control circuit,    the switching power supply circuit is provided with: A rectifier bridge diode for rectification; a primary-side smoothing capacitor that smoothes the rectified DC; and the DC that is smoothed by the aforementioned primary-side smoothing capacitor is based on the pulse signal from the pulse signal generating means The periodic ON/OFF switching of the switching element is converted into a pulse wave of the AC, which is transformed into a preset AC voltage and transmitted to the switching transformer on the secondary side; the AC that is transmitted to the secondary side is rectified. Secondary side diode; and a secondary side smoothing capacitor that smoothes the rectified DC and outputs it.    The control circuit is based on the command signal and the detection result on the output side of the switching power supply circuit, and adjusts the pulse signal The pulse width of the pulse signal obtained by the generator is used to control the ON/OFF switching of the aforementioned switching element.   The inductive load drive circuit is:   In addition, it has: an energy recovery circuit, which makes the inductive load current when the current decreases. The back electromotive force of the inductive load is recovered while it is generated, and the aforementioned energy recovery circuit includes:    in the same iron core, there are two primary side coils connected in series and opposite polarity to the inductive load with different resistance values, and a primary coil connected to the switching transformer A transformer for recovery of a secondary coil on the secondary side; and a primary side coil with a relatively small resistance value among the two primary coils, arranged in series with the secondary coil based on the recovery command signal from the control circuit. The pulse signal generated by the pulse signal generator operates to control the recovery control element of the current flowing to the primary side coil of the aforementioned low resistance.    The aforementioned control circuit makes the recovery control element relative to the aforementioned recovery control element when the current of the inductive load decreases. By adjusting the pulse width of the pulse signal obtained by the second pulse signal generating device, the recovery control element is turned off for a certain period of time, thereby generating the back electromotive force of the inductive load while increasing the relative resistance of the recovery transformer. Current flows through the primary coil of the resistor, thereby changing the magnetic flux of the iron core and transferring energy to the corresponding secondary coil. [0017] The inductive load drive circuit of the invention described in claim 2 is in the inductive load drive circuit described in claim 1,    is additionally provided with a second recovery control element, which is the same as the aforementioned large resistance of the recovery transformer The side coils are arranged in series to limit the current flowing to the high-resistance primary-side coil so that the voltage when the recovery control element of the small-resistance primary-side coil is turned off becomes constant. (Effects of the Invention)   [0018] The inductive load drive circuit of the present invention is configured to switch the power supply circuit and additionally includes an energy recovery circuit obtained by a recovery transformer connected in series with the primary coil and the inductive load, thereby enabling When the current of the inductive load insulated from the power supply side decreases, the back electromotive force of the inductive load is generated and recovered well. Therefore, there is no heat loss and high response when the inductive load current stops is efficiently realized. In particular, the primary side of the recovery transformer is formed to form an energy recovery circuit with two coils of opposite polarities, a large resistance and a small resistance. In a steady state, it is non-inductive and prevents current rise when the load current increases. At the same time, the speed is slow, and the current of the small-resistance primary coil is controlled by the recovery control element controlled by the PWM drive. This allows high-speed control of the load current reduction rate when the inductive load stops, so it has a more efficient It also has the effect of high-response current control of inductive loads.

[0020] 本發明中之感應負載驅動電路係具有:切換電源電路、及控制電路,該切換電源電路係具備有:將來自電源的交流進行整流的整流橋式二極體;將經整流的直流平滑化的一次側平滑電容器;將藉由前述一次側平滑電容器被平滑化的直流,藉由以根據來自脈衝訊號發生手段的脈衝訊號的周期的切換元件的ON/OFF切換,被轉換成脈衝波的交流者,變壓成預先設定的交流電壓而傳達至二次側的切換變壓器;將被傳達至二次側的交流進行整流的二次側二極體;及將經整流的直流更加平滑化而進行輸出的二次側平滑電容器,該控制電路係根據指令訊號與前述切換電源電路的輸出側的檢測結果,調整藉由前述脈衝訊號發生裝置所得之脈衝訊號的脈衝寬度,來控制前述切換元件的ON/OFF切換,另外具備有:能量回收電路,其係在感應負載的電流減少時,一邊使該感應負載的反電動勢發生一邊回收。   [0021] 藉由以上構成,本發明係藉由能量回收電路,在感應負載的電流減少時,可將該感應負載的反電動勢,在無伴隨因消耗所致之發熱的情形下,良好地回收,實現感應負載停止時的高響應性者。   [0022] 亦即,本發明之能量回收電路係包含:在同一鐵心具有以串聯且彼此相反極性連接在前述感應負載之電阻值不同的二個一次側線圈、及連接在前述切換變壓器的一次側的一個二次側線圈的回收用變壓器;及與前述二個一次側線圈之中相對電阻值小的小電阻一次側線圈串聯配置而按照根據來自前述控制電路的回收指令訊號之藉由第2脈衝訊號發生裝置所得之脈衝訊號進行動作,來控制流至前述小電阻一次側線圈的電流的回收控制元件,前述控制電路係在前述感應負載的電流減少時使藉由相對前述回收控制元件之前述第2脈衝訊號發生裝置所得之脈衝訊號的脈衝寬度調整,將前述回收控制元件進行OFF控制一定時間,藉此一邊使前述感應負載的反電動勢發生一邊對前述回收用變壓器的相對電阻值大的大電阻一次側線圈流通電流,藉此使鐵芯磁通量改變而使能量傳達至相對應的二次側線圈者。   [0023] 在以上之能量回收電路中,小電阻一次側線圈係若減小繞組電阻至可忽略電阻損失的程度即可。在對感應負載的電流為一定時,基於線圈電阻值的平衡,電流幾乎流至小電阻一次側線圈來將變壓器/鐵芯進行激磁,但是若相對於小電阻一次側線圈的電感,電流的增加速度較大時,因電流流至反向捲繞的大電阻一次側線圈而無感應化,防止電流響應遲緩。   [0024] 接著,若增加感應負載電流的減少速度,將回收控制元件形成為OFF一定時間,藉此,全部電流欲流至大電阻一次側線圈,因此在大電阻一次側線圈的兩端發生高電壓,且改變變壓器/鐵芯的激磁,因此在回收用變壓器的二次側線圈流通感應電流而回收能量。此時,感應負載電流的減少速度係可藉由使以控制電路予以PWM驅動控制的回收控制元件的負載比進行可變而高速控制。   [0025] 此外,在本發明中,另外具備有與前述回收用變壓器的前述大電阻一次側線圈串聯配置的第2回收控制元件,可以將前述小電阻一次側線圈的前述回收控制元件呈OFF時的電壓成為一定的方式,限制流至前述大電阻一次側線圈的電流。藉此,電流變少,即使大電阻一次側線圈的兩端電壓減少,亦抑制對二次側線圈的傳達量的減少,而且因第2回收控制元件的損失份,可達成感應負載電流的減少速度的高速化。 [實施例]   [0026] 將本發明之一實施例之感應負載驅動電路的概略構成圖顯示於圖1。本實施例之感應負載驅動電路1係具備有切換電源電路10作為基本構成。亦即,具備有:將來自供給電源12的交流進行整流的橋式二極體13;將經整流的直流平滑化的一次側平滑電容器14;將藉由一次側平滑電容器14被平滑化的直流,以根據在控制電路20藉由脈衝訊號發生裝置24所發生的脈衝訊號的周期進行ON/OFF切換而轉換成脈衝波的交流的切換元件(FET)15;將脈衝波交流,由一次側線圈LP對二次側線圈LS變壓成預先設定的電壓來進行傳達的切換變壓器16;將被傳達至二次側的交流進行整流的二次側整流二極體17;及將經整流的直流更加平滑化而送至感應負載(電磁線圈)11的二次側平滑電容器18。   [0027] 此外,在切換電源電路10的輸出側係配置有電流感測器25,在控制電路20中,係根據藉由指令訊號21與電流感測器25所得之檢測結果,進行電流的反饋控制。   [0028] 接著,在本實施例中,在具備有以上構成的切換電源電路10另外設有回收電磁線圈電流減少時的反電動勢的能量回收電路30。該能量回收電路30係具備有一次側被串聯連接在電磁線圈11的回收用變壓器31,藉由該一次側線圈被進行PWM控制,能量被傳達至二次側者。   [0029] 具體而言,回收用變壓器31係在同一鐵心具有以串聯且彼此相反極性連接在電磁線圈11之相對電阻值大的大電阻一次側線圈LP1與相對電阻值小的小電阻一次側線圈LP2的二個一次側線圈;及連接在切換變壓器16的一次側的一個回收用二次側線圈RLS者。接著,具備有:與二個一次側線圈之中的小電阻一次側線圈LP2串聯配置而按照根據來自控制電路20的回收指令訊號之藉由第2脈衝訊號發生裝置33所得之脈衝訊號進行動作,來控制流至小電阻一次側線圈LP2的電流的回收控制元件32。   [0030] 在該能量回收電路30中,由於大電阻一次側線圈LP1與小電阻一次側線圈LP2為相反極性,因此電流增加時,因該等大電阻一次側線圈LP1與小電阻一次側線圈LP2被激磁而無感應化,防止電磁線圈電流的上升速度遲緩。   [0031] 此外,在本實施例中,在電磁線圈11的電流減少時,控制電路20係由相對回收控制元件32之第2脈衝訊號發生裝置33使脈衝訊號的脈衝寬度改變,而將回收控制元件32進行OFF控制一定時間,藉此一邊使電磁線圈11的反電動勢發生一邊對大電阻一次側線圈LP1流通電流,藉此使鐵芯磁通量改變而使能量傳達至回收用二次側線圈RLS。   [0032] 伴隨此,由於全部電流欲流至大電阻一次側線圈LP1,因此在大電阻一次側線圈LP1的兩端發生高電壓,且改變變壓器/鐵芯的激磁,因此在回收用二次側線圈RLS流通感應電流,能量被回收。此時,電磁線圈電流的減少速度係可藉由使予以PWM驅動控制的回收控制元件32的負載比進行可變而高速控制。   [0033] 在此顯示藉由與不具能量回收電路30的感應負載驅動電路的比較試驗,確認藉由能量回收電路30所得之效果的結果。在本比較試驗中,將由圖5(a)所示之習知之切換電源電路構成所成之感應負載驅動電路100作為對照,在該感應負載驅動電路100的構成組合能量回收電路30的構成而成之圖1所示之感應負載驅動電路1中,測定電磁線圈停止時的電磁線圈電流的減少,比較其降低特性。將結果顯示於圖2的圖表。   [0034] 圖2係在作為時間軸的橫軸中,將由電磁線圈電流一定狀態為電磁線圈停止時(電流供給停止時)設為0(msec),將隨著時間經過的電流值(A)顯示於縱軸者。   [0035] 由圖2清楚可知,相對於無能量回收電路30且未進行電磁線圈的電動勢回收之作為對照的感應負載驅動電路之情形下的電流值的變化曲線X,在藉由能量回收電路30回收電磁線圈的電動勢的圖1的感應負載驅動電路1中的電流值的變化曲線Y中,電磁線圈電流的減少(降低)速度大,且其響應性非常高。   [0036] 此外,經時性測定圖2中所測定出的反電動勢的回收中的電磁線圈電流減少時的回收電力,相對於時間:橫軸(msec),在縱軸取回收電力(W),將其變化曲線Z顯示於圖3的圖表。由該圖3可知,回收電力係在電磁線圈電流減少開始瞬後急遽增大,藉由能量回收電路30所為之電動勢的回收有助於電磁線圈電流減少時的高響應。   [0037] 其中,在圖1的能量回收電路30中,若反電動勢的回收進展而電流變小時,大電阻一次側線圈LP1的兩端電壓減少,且回收亦減低。因此,以圖1所示之能量回收電路30的構成為基本,如圖4所示,藉由形成為另外具備有與大電阻一次側線圈LP1作串聯配置的第2回收控制元件(FET)41的能量回收電路40的構成,可解決該問題。   [0038] 亦即,在能量回收電路40中,可以將小電阻一次側線圈LP2的回收控制元件32成為OFF狀態時的電壓成為一定的方式,以第2回收控制元件41限制流至大電阻一次側線圈LP1的電流,因此藉此即使大電阻一次側線圈LP1的兩端電壓減少,亦可抑制對回收用二次側線圈RLS的傳達量的減少,而且因第2回收控制元件41的損失份,可達成電磁線圈電流的減少速度的高速化。[0020] The inductive load driving circuit in the present invention has: a switching power supply circuit and a control circuit. The switching power supply circuit is provided with: a rectifier bridge diode that rectifies the AC from the power source; and the rectified DC A smoothed primary side smoothing capacitor; the direct current smoothed by the aforementioned primary side smoothing capacitor is converted into a pulse wave by ON/OFF switching of the switching element according to the period of the pulse signal from the pulse signal generating means The AC, which transforms into a preset AC voltage and transmits it to the secondary side switching transformer; the secondary side diode that rectifies the AC transmitted to the secondary side; and smoothes the rectified DC As for the secondary side smoothing capacitor for output, the control circuit adjusts the pulse width of the pulse signal obtained by the pulse signal generator according to the command signal and the detection result of the output side of the switching power circuit to control the switching element The ON/OFF switching of the inductive load is additionally equipped with: an energy recovery circuit, which recovers the back electromotive force of the inductive load when the current of the inductive load decreases. [0021] With the above constitution, the present invention uses an energy recovery circuit, when the current of the inductive load is reduced, the back electromotive force of the inductive load can be recovered well without the heat caused by consumption. , To achieve high responsiveness when the inductive load stops. [0022] That is, the energy recovery circuit of the present invention includes two primary side coils connected in series with opposite polarities to the aforementioned inductive load in the same iron core, and the primary side of the switching transformer connected to the primary side. A transformer for the recovery of a secondary side coil; and the primary side coil with a relatively small resistance value among the two primary side coils is arranged in series with the second pulse according to the recovery command signal from the control circuit The pulse signal obtained by the signal generating device operates to control the recovery control element of the current flowing to the primary side coil of the small resistance. The control circuit makes the recovery control element relative to the recovery control element when the current of the inductive load decreases. 2. Adjust the pulse width of the pulse signal obtained by the pulse signal generator, and turn off the aforementioned recovery control element for a certain period of time, thereby generating the back electromotive force of the aforementioned inductive load and resisting the large resistance of the aforementioned recovery transformer. The primary side coil flows current, thereby changing the magnetic flux of the iron core to transfer energy to the corresponding secondary side coil.  [0023] In the above energy recovery circuit, the small-resistance primary side coil can be reduced to a negligible resistance loss. When the current to the inductive load is constant, based on the balance of the coil resistance, the current almost flows to the low-resistance primary coil to excite the transformer/iron core, but if compared to the inductance of the low-resistance primary coil, the current increases When the speed is high, the current flows to the reverse-wound high-resistance primary coil without induction, preventing the current response from being slow. [0024] Next, if the reduction speed of the inductive load current is increased, the recovery control element is turned OFF for a certain period of time, whereby all the current is going to flow to the high resistance primary coil, so high resistance occurs at both ends of the high resistance primary coil. The voltage changes the excitation of the transformer/iron core, so the induced current flows through the secondary coil of the recovery transformer to recover energy. At this time, the reduction speed of the inductive load current can be controlled at high speed by changing the duty ratio of the recovery control element that is PWM-driven by the control circuit. [0025] In addition, in the present invention, a second recovery control element arranged in series with the large resistance primary coil of the recovery transformer is additionally provided, and the recovery control element of the low resistance primary coil can be turned off. The voltage becomes a constant way to limit the current flowing to the aforementioned high-resistance primary coil. As a result, the current is reduced, and even if the voltage across the primary coil with large resistance decreases, the reduction in the amount of transmission to the secondary coil is suppressed, and the inductive load current can be reduced due to the loss of the second recovery control element. Increased speed. [Embodiment]   [0026] A schematic configuration diagram of an inductive load driving circuit according to an embodiment of the present invention is shown in FIG. 1. The inductive load driving circuit 1 of this embodiment includes a switching power supply circuit 10 as a basic structure. That is, it is provided with: a bridge diode 13 that rectifies the alternating current from the power supply 12; a primary side smoothing capacitor 14 that smoothes the rectified direct current; and a direct current that is smoothed by the primary side smoothing capacitor 14 , With an AC switching element (FET) 15 that converts the pulse wave by ON/OFF switching according to the cycle of the pulse signal generated by the pulse signal generator 24 in the control circuit 20; the pulse wave is exchanged by the primary coil LP transforms the secondary side coil LS into a preset voltage for transmission; the secondary side rectifier diode 17 rectifies the alternating current transmitted to the secondary side; and further changes the rectified direct current The smoothing is sent to the secondary side smoothing capacitor 18 of the inductive load (electromagnetic coil) 11. [0027] In addition, a current sensor 25 is arranged on the output side of the switching power supply circuit 10. In the control circuit 20, current feedback is performed based on the detection result obtained by the command signal 21 and the current sensor 25 control.  [0028] Next, in the present embodiment, the switching power supply circuit 10 having the above configuration is additionally provided with an energy recovery circuit 30 that recovers the back electromotive force when the solenoid current decreases. The energy recovery circuit 30 is provided with a recovery transformer 31 connected in series to the electromagnetic coil 11 on the primary side, and the primary side coil is PWM controlled so that energy is transmitted to the secondary side. [0029] Specifically, the recovery transformer 31 is connected to the electromagnetic coil 11 in series with opposite polarities on the same iron core, and has a large-resistance primary coil LP1 with a large relative resistance value and a small-resistance primary coil with a small relative resistance value. Two primary side coils of LP2; and a secondary side coil RLS for recovery connected to the primary side of the switching transformer 16. Next, it is equipped with: arranging in series with the small-resistance primary coil LP2 among the two primary coils and operating in accordance with the pulse signal obtained by the second pulse signal generating device 33 according to the recovery command signal from the control circuit 20, The recovery control element 32 to control the current flowing to the low-resistance primary side coil LP2. [0030] In the energy recovery circuit 30, since the large-resistance primary coil LP1 and the low-resistance primary coil LP2 have opposite polarities, when the current increases, the large-resistance primary coil LP1 and the low-resistance primary coil LP2 Excited without induction, to prevent the slow rise of the solenoid current. [0031] In addition, in this embodiment, when the current of the electromagnetic coil 11 decreases, the control circuit 20 uses the second pulse signal generating device 33 opposite to the recovery control element 32 to change the pulse width of the pulse signal to control the recovery The element 32 performs OFF control for a certain period of time, thereby generating a counter electromotive force of the electromagnetic coil 11 while flowing a current through the high-resistance primary coil LP1, thereby changing the core magnetic flux and transferring energy to the recovery secondary coil RLS. [0032] Accompanying this, since all the current is going to flow to the high-resistance primary coil LP1, a high voltage is generated across the high-resistance primary coil LP1, and the transformer/iron core excitation is changed, so on the secondary side for recovery The induction current flows through the coil RLS, and the energy is recovered. At this time, the reduction speed of the solenoid current can be controlled at a high speed by changing the duty ratio of the recovery control element 32 that is PWM drive-controlled.  [0033] The results of the comparison test with the inductive load drive circuit without the energy recovery circuit 30 to confirm the effect obtained by the energy recovery circuit 30 are shown here. In this comparative test, the inductive load drive circuit 100 constructed by the conventional switching power supply circuit shown in FIG. 5(a) is used as a control. The structure of the inductive load drive circuit 100 is combined with the structure of the energy recovery circuit 30. In the inductive load drive circuit 1 shown in Fig. 1, the reduction of the solenoid current when the solenoid is stopped is measured, and the reduction characteristics are compared. The results are shown in the graph in Figure 2. [0034] FIG. 2 is on the horizontal axis as the time axis, the current from the electromagnetic coil is set to 0 (msec) when the electromagnetic coil is in a constant state (when the current supply is stopped), and the current value (A) with the passage of time Those shown on the vertical axis. [0035] It can be clearly seen from FIG. 2 that the change curve X of the current value in the case of the inductive load drive circuit without the energy recovery circuit 30 and the electromotive force recovery of the electromagnetic coil as a control, in the case of the energy recovery circuit 30 In the change curve Y of the current value in the inductive load drive circuit 1 of FIG. 1 that recovers the electromotive force of the electromagnetic coil, the reduction (decrease) speed of the electromagnetic coil current is large, and its responsiveness is very high. [0036] In addition, the recovered power when the solenoid current is reduced in the recovery of the back electromotive force measured in FIG. 2 is measured over time, with respect to time: the horizontal axis (msec), and the recovered power (W) is taken on the vertical axis. , The change curve Z is shown in the graph of Figure 3. It can be seen from FIG. 3 that the recovered power system increases rapidly immediately after the electromagnetic coil current decreases, and the recovery of the electromotive force by the energy recovery circuit 30 contributes to a high response when the electromagnetic coil current decreases.  [0037] Wherein, in the energy recovery circuit 30 of FIG. 1, if the recovery of the back electromotive force progresses and the current becomes smaller, the voltage across both ends of the large-resistance primary coil LP1 decreases, and the recovery also decreases. Therefore, based on the configuration of the energy recovery circuit 30 shown in FIG. 1, as shown in FIG. 4, it is formed to additionally include a second recovery control element (FET) 41 arranged in series with the large resistance primary coil LP1. The structure of the energy recovery circuit 40 can solve this problem. [0038] That is, in the energy recovery circuit 40, the voltage when the recovery control element 32 of the low-resistance primary side coil LP2 is turned off can be constant, and the second recovery control element 41 can restrict the flow to the high-resistance primary The current of the side coil LP1, therefore, even if the voltage across the both ends of the high-resistance primary side coil LP1 decreases, the reduction in the amount of transmission to the secondary side coil RLS for recovery can be suppressed, and the loss due to the second recovery control element 41 , Can achieve the speed of reduction of electromagnetic coil current.

[0039]1、100‧‧‧感應負載驅動電路10‧‧‧切換電源電路11、111‧‧‧電磁線圈(感應負載)12、112‧‧‧供給電源13、113‧‧‧橋式二極體14、114‧‧‧平滑電容器(一次側)15、115‧‧‧切換元件16、116‧‧‧切換變壓器LP、Lp‧‧‧一次側線圈LS、Ls‧‧‧二次側線圈17、35、117‧‧‧整流二極體18、118‧‧‧平滑電容器(二次側)20‧‧‧控制電路21、121‧‧‧指令訊號24、124‧‧‧脈衝訊號發生裝置25、125‧‧‧電流感測器30、40‧‧‧能量回收電路31‧‧‧回收用變壓器LP1‧‧‧大電阻一次側線圈LP2‧‧‧小電阻一次側線圈RLS‧‧‧回收用二次側線圈32‧‧‧回收控制元件33‧‧‧第2脈衝訊號發生裝置41‧‧‧第2回收控制元件[0039]1, 100‧‧‧Inductive load drive circuit 10‧‧‧Switching power supply circuit 11,111‧‧‧Electromagnetic coil (inductive load) 12,112‧‧‧Power supply 13,113‧‧‧Bridge diode Body 14, 114‧‧‧Smoothing capacitor (primary side) 15, 115‧‧‧Switching element 16,116‧‧‧Switching transformer LP, Lp‧‧‧ Primary side coil LS, Ls‧‧‧Secondary side coil 17, 35、117‧‧‧Rectifier diode 18,118‧‧‧Smoothing capacitor (secondary side) 20‧‧‧Control circuit 21,121‧‧‧Command signal 24,124‧‧‧Pulse signal generating device 25,125 ‧‧‧Current sensor 30, 40‧‧‧Energy recovery circuit 31‧‧‧Recovery transformer LP1‧‧‧High resistance primary coil LP2‧‧‧Small resistance primary coil RLS‧‧‧Recovery secondary side Coil 32‧‧‧Recovery control element 33‧‧‧Second pulse signal generator 41‧‧‧Second recovery control element

[0019]   圖1係本發明之一實施例之感應負載驅動電路的概略構成圖。   圖2係顯示能量回收電路之有無中的電磁線圈降低特性的圖表(橫軸:時間[msec],縱軸:電流[A])。   圖3係顯示圖2之能量回收時之電力回收特性的圖表(橫軸:時間[msec],縱軸:回收電力[W]與電磁線圈電流[A])。   圖4係顯示改良圖1之能量回收電路者的部分電路圖。   圖5係顯示具有切換電源電路之習知之感應負載驅動電路之例的概略構成圖,(a)係電流控制電路圖,(b)係顯示感應負載電流OFF時的動作的部分電路圖。[0019] "Figure 1" is a schematic configuration diagram of an inductive load drive circuit according to an embodiment of the present invention.   Figure 2 is a graph showing the reduction characteristics of the electromagnetic coil in the presence or absence of an energy recovery circuit (horizontal axis: time [msec], vertical axis: current [A]).   Figure 3 is a graph showing the power recovery characteristics during energy recovery in Figure 2 (horizontal axis: time [msec], vertical axis: recovered power [W] and solenoid current [A]).   Figure 4 is a partial circuit diagram showing the improvement of the energy recovery circuit of Figure 1.   Figure 5 is a schematic configuration diagram showing an example of a conventional inductive load driving circuit with a switching power supply circuit, (a) is a current control circuit diagram, (b) is a partial circuit diagram showing the operation when the inductive load current is OFF.

1‧‧‧感應負載驅動電路 1.‧‧Inductive load drive circuit

10‧‧‧切換電源電路 10‧‧‧Switching power circuit

11‧‧‧電磁線圈(感應負載) 11‧‧‧Electromagnetic coil (inductive load)

12‧‧‧供給電源 12‧‧‧Power supply

13‧‧‧橋式二極體 13‧‧‧Bridge Diode

14‧‧‧平滑電容器(一次側) 14‧‧‧Smoothing capacitor (primary side)

15‧‧‧切換元件 15‧‧‧Switching element

16‧‧‧切換變壓器 16‧‧‧Switching transformer

17、35‧‧‧整流二極體 17, 35‧‧‧rectifier diode

18‧‧‧平滑電容器(二次側) 18‧‧‧Smoothing capacitor (secondary side)

20‧‧‧控制電路 20‧‧‧Control circuit

21‧‧‧指令訊號 21‧‧‧Command signal

24‧‧‧脈衝訊號發生裝置 24‧‧‧Pulse signal generator

25‧‧‧電流感測器 25‧‧‧Current Sensor

30‧‧‧能量回收電路 30‧‧‧Energy recovery circuit

31‧‧‧回收用變壓器 31‧‧‧Recycling transformer

32‧‧‧回收控制元件 32‧‧‧Recycling control components

33‧‧‧第2脈衝訊號發生裝置 33‧‧‧The second pulse signal generator

LP‧‧‧一次側線圈 LP‧‧‧ Primary side coil

LS‧‧‧二次側線圈 LS‧‧‧Secondary coil

LP1‧‧‧大電阻一次側線圈 LP1‧‧‧Large resistance primary coil

LP2‧‧‧小電阻一次側線圈 LP2‧‧‧Small resistance primary coil

RLS‧‧‧回收用二次側線圈 RLS‧‧‧Secondary coil for recycling

Claims (2)

一種感應負載驅動電路,其係具有:切換電源電路、及控制電路,該切換電源電路係具備有:將來自電源的交流進行整流的整流橋式二極體;將經整流的直流平滑化的一次側平滑電容器;將藉由前述一次側平滑電容器被平滑化的直流,藉由以根據來自脈衝訊號發生裝置的脈衝訊號的周期的切換元件的ON/OFF切換,被轉換成脈衝波的交流者,變壓成預先設定的交流電壓而傳達至二次側的切換變壓器;將被傳達至二次側的交流進行整流的二次側二極體;及將經整流的直流更加平滑化而進行輸出的二次側平滑電容器,該控制電路係根據指令訊號與前述切換電源電路的輸出側的檢測結果,調整藉由前述脈衝訊號發生裝置所得之脈衝訊號的脈衝寬度,來控制前述切換元件的ON/OFF切換,該感應負載驅動電路之特徵為:另外具備有:能量回收電路,其係在感應負載的電流減少時,一邊使該感應負載的反電動勢發生一邊回收,前述能量回收電路係包含:在同一鐵心具有以串聯且彼此相反極性連接在前述感應負載之電阻值不同的二個一次側線圈、及連接在前述切換變壓器的一次側的一個二次側線圈的回收用變壓器;及 與前述二個一次側線圈之中相對電阻值小的小電阻一次側線圈串聯配置而按照根據來自前述控制電路的回收指令訊號之藉由第2脈衝訊號發生裝置所得之脈衝訊號進行動作,來控制流至前述小電阻一次側線圈的電流的回收控制元件,前述控制電路係在前述感應負載的電流減少時使藉由相對前述回收控制元件之前述第2脈衝訊號發生裝置所得之脈衝訊號的脈衝寬度調整,將前述回收控制元件進行OFF控制一定時間,藉此一邊使前述感應負載的反電動勢發生一邊對前述回收用變壓器的相對電阻值大的大電阻一次側線圈流通電流,藉此使鐵芯磁通量改變而使能量傳達至相對應的二次側線圈者。 An inductive load drive circuit, which has: a switching power supply circuit and a control circuit. The switching power supply circuit is provided with: a rectifier bridge diode that rectifies AC from the power source; a primary circuit that smoothes the rectified DC Side smoothing capacitor: The direct current smoothed by the aforementioned primary side smoothing capacitor is converted into a pulse wave AC by switching on/off the switching element according to the period of the pulse signal from the pulse signal generator, A switching transformer that transforms the voltage into a preset AC voltage and transmits it to the secondary side; a secondary side diode that rectifies the AC that is transmitted to the secondary side; and smoothes the rectified DC to output Secondary side smoothing capacitor. The control circuit adjusts the pulse width of the pulse signal obtained by the pulse signal generator according to the command signal and the detection result of the output side of the switching power supply circuit to control the ON/OFF of the switching element Switch, the inductive load driving circuit is characterized by: in addition, it has: an energy recovery circuit, which recovers the back electromotive force of the inductive load when the current of the inductive load decreases, and the aforementioned energy recovery circuit includes: The iron core has a recovery transformer with two primary side coils connected in series and opposite polarity to the aforementioned inductive load with different resistance values, and a secondary side coil connected to the primary side of the aforementioned switching transformer; and It is arranged in series with the primary side coil with a relatively small resistance value among the two primary side coils and operates according to the pulse signal obtained by the second pulse signal generating device according to the recovery command signal from the above-mentioned control circuit to control The recovery control element of the current flowing to the primary side coil of the small resistance, the control circuit makes the pulse width of the pulse signal obtained by the second pulse signal generating device of the recovery control element when the current of the inductive load decreases Adjust to turn off the recovery control element for a certain period of time, so as to generate the back electromotive force of the inductive load while flowing current through the large resistance primary coil of the recovery transformer with a large relative resistance value, thereby making the core magnetic flux Change so that the energy is transmitted to the corresponding secondary side coil. 如申請專利範圍第1項之感應負載驅動電路,其中,前述能量回收電路係另外具備有:第2回收控制元件,其係與前述回收用變壓器的前述大電阻一次側線圈串聯配置;及定電壓二極體,其係被插入在該第2回收控制元件的閘極側,若前述小電阻一次側線圈的前述回收控制元件呈OFF時流至一次側線圈的電流減少而在前述大電阻一次側線圈所發生的電壓低於前述第2回收控制元件的閘極臨限值電壓與前述定電壓二極體的電壓的和時,使前述第2回收控制元件的汲極-源極間電壓上升而將前述第2回收控制元件 的汲極-源極間電壓與前述大電阻一次側線圈的電壓的和的電壓形成為一定,且將前述第2回收控制元件的汲極-源極間電壓與前述大電阻一次側線圈的電壓的和,以不會成為前述第2回收控制元件的閘極臨限值電壓與前述定電壓二極體的電壓的和的電壓以下的方式進行控制。 For example, the inductive load driving circuit of the first item of the patent application, wherein the energy recovery circuit is additionally equipped with: a second recovery control element, which is arranged in series with the large resistance primary coil of the recovery transformer; and a constant voltage A diode is inserted on the gate side of the second recovery control element. If the recovery control element of the low resistance primary side coil is turned off, the current flowing to the primary side coil decreases and the high resistance primary side coil When the generated voltage is lower than the sum of the gate threshold voltage of the second recovery control element and the voltage of the constant voltage diode, the drain-source voltage of the second recovery control element is increased to reduce The aforementioned second recovery control element The voltage of the sum of the drain-source voltage and the voltage of the high-resistance primary side coil is constant, and the drain-source voltage of the second recovery control element and the voltage of the high-resistance primary coil The sum is controlled so as not to become the voltage below the sum of the gate threshold voltage of the second recovery control element and the voltage of the constant voltage diode.
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