TWI352520B - Orthogonal frequency division multiplexing system - Google Patents
Orthogonal frequency division multiplexing system Download PDFInfo
- Publication number
- TWI352520B TWI352520B TW96136267A TW96136267A TWI352520B TW I352520 B TWI352520 B TW I352520B TW 96136267 A TW96136267 A TW 96136267A TW 96136267 A TW96136267 A TW 96136267A TW I352520 B TWI352520 B TW I352520B
- Authority
- TW
- Taiwan
- Prior art keywords
- signal
- channel
- channel estimation
- frequency division
- symbol
- Prior art date
Links
Description
1352520 九、發明說明: 【發明所屬之技術領域】 本發明係有關於一種正交分頻多工傳輸系統之通道 估測裝置與方法,尤其是指一種以完善的通道估測裝置與 方法來追蹤通道的快速變化,以提昇系統效能的目的。 【先前技術】 按’正父分頻多工傳輸〔Orthogonal Frequency Division Multiplexing; OFDM〕系統在無線通訊中,已 有許多研究被提出。在行動通訊系統中,無線通道通常是 頻率選擇性〔frequency selective〕及時變〔time varying 〕的,雖然,正交分頻多工傳輸〔〇FDM〕系統有很好對抗 頻率選擇衰落的能力、然而先決條件是接收端要有一個良 = 正交一傳輸〔_ 接續,在#· $ 4+ 常會在傳輪㈣以Γ,為了瞭駐知㈣道特性,通 是接收端已知的領航訊號或訓練訊號,領航訊號 號來進行通道估訊,、所以在純端相藉由領航訊 時,為了增加傳輸道特性之資訊。在使用領航訊號 工傳輸〔_〕寬’領航訊號只使用在正交分頻多 這些子載波進行通^特定子載波間,通道估測也只針對 到的子載波資訊對性的估測,然後再利用這些估測得 性估測,所使用^它非領航訊號的子載波進行通道特 I用之方法多為内插法。 然而’在弁俞枯1352520 IX. Description of the Invention: [Technical Field] The present invention relates to a channel estimation apparatus and method for an orthogonal frequency division multiplexing transmission system, and more particularly to tracking a perfect channel estimation apparatus and method Rapid changes in the channel to enhance system performance. [Prior Art] Many studies have been proposed in the wireless communication of the Orthogonal Frequency Division Multiplexing (OFDM) system. In mobile communication systems, wireless channels are usually frequency selective and time varying, although orthogonal frequency division multiplexing (〇FDM) systems have good resistance to frequency selective fading. The precondition is that the receiving end should have a good = orthogonal one transmission [_ continuation, in #· $ 4+ often in the transmission wheel (four) Γ, in order to the station (four) characteristics, the pass is the pilot signal known to the receiving end or The training signal and the pilot signal number are used for channel estimation, so in order to increase the information of the transmission channel characteristics when the pure end is used for the pilot. In the use of pilot signal transmission [_] wide 'navigation signal only use these subcarriers in the orthogonal frequency division between the specific subcarriers, the channel estimation is only for the estimation of the subcarrier information, and then Using these estimates, it is mostly the interpolation method used for the subcarriers of the non-navigable signals. However,
術中,很多正交分頻多工傳輸〔0FDM 5 1352520 明之: 首先’請參閱第一圖所示,為本發明之正交分頻多工 傳輸〔0FDM〕系統之方塊圖’其主要係以傳送端將二位元 之資訊資料經過調變即訊號對應(110)後,經由串列轉並 列(120)成為串列資料後’再插入錯誤偵測訊號(130)〔 error detection〕’ 成為在頻域上〔frequency domain〕 的調變子載波訊號义W,此錯誤訊號可用來偵測接收訊號 之錯誤,此調變訊號再經由快速反傅利葉轉換(140) 〔IFFT〕將頻域的訊號义㈨轉換為時域訊號(141)〔 time domain ] χ(«): x(n) = IDFT{x(k)} = ^ X(k)ej2nkn/N, A=0 « = 0,1,.·.,iV-l ( —) 其中#為正交分頻多工傳輸〔OFDM〕系統之子載波 個數。During operation, many orthogonal frequency division multiplexing transmissions [0FDM 5 1352520: First, please refer to the first figure, which is the block diagram of the orthogonal frequency division multiplexing transmission (OFDM) system of the present invention. After the information of the two bits is modulated, that is, the signal is corresponding (110), after the serialization of the serial data (120) becomes the serial data, the 're-insertion error detection signal (130) is obtained. The frequency domain of the modulated subcarrier signal is W. This error signal can be used to detect the error of the received signal. The modulated signal is then converted to the frequency domain by fast inverse Fourier transform (140) [IFFT]. Convert to time domain signal (141) [ time domain ] χ(«): x(n) = IDFT{x(k)} = ^ X(k)ej2nkn/N, A=0 « = 0,1,.· iV-1 (-) where # is the number of subcarriers of the Orthogonal Frequency Division Multiplexing (OFDM) system.
為了防止接收訊號之符號間的干擾〔inter-symbol interference〕現象發生,通常在兩個時域訊號之符號間 插入防護區間(150),成為正交分頻多工傳輸〔OFDM〕系 統之傳輸訊號(151)xg(«):In order to prevent the inter-symbol interference phenomenon of the received signal, a guard interval (150) is usually inserted between the symbols of the two time-domain signals to become a transmission signal of the orthogonal frequency division multiplexing (OFDM) system. (151)xg(«):
X x(N + n\ n = -Ng,-Ng x(4 w = 0,1,···,— 1 其中义為插入防護區間(150)的長度。 插入防護區間(150)的時域訊號經由並列轉串列(160) 後,經過發射機(170)發射後通過無線通道(180)到接收機 (210),接收機接收到的訊號可表示: 7 yg(n) = («)® h(n)+ w{n) (三) _其中為通道的脈衝響應,而則是可加性之X x(N + n\ n = -Ng, -Ng x(4 w = 0,1,···, - 1 where is the length of the insertion guard interval (150). Insert the time domain of the guard interval (150) After the signal is transmitted to the receiver (210) via the parallel channel (160) and transmitted through the transmitter (170), the signal received by the receiver can be expressed as: 7 yg(n) = («) ® h(n)+ w{n) (c) _ where is the impulse response of the channel, but it is additive
冋斯白雜訊(190)〔 Additive White Gaussian Noise, AWGN 〕®為兩個訊號之旋積(convolution)符號。 在接收端之解調步驟是,經過串列轉並列(22〇)後先 把移除防護區間(23〇),然後經過快速傅利葉轉換(24〇)〔 IFFT〕將時域上轉換到頻域上,成為頻域之接收訊號(241) Yik):Additive White Gaussian Noise (AWGN)® is a convolution symbol for two signals. The demodulation step at the receiving end is to remove the guard interval (23〇) after serial concatenation (22〇), and then up-convert the time domain to the frequency domain through fast Fourier transform (24〇) [ IFFT]. On, become the receiving signal in the frequency domain (241) Yik):
r(k)=,DFT{y(n)}=±^y^ ~J2nbt / N 灸=0,1,1 (四) 在接收訊號中可以執行接收訊號之錯誤偵測 (250),以偵測所接收之訊號是否有錯誤,假設防護區間 的長度大於通道脈衝㈣'的長度,因此正交分射工傳輸 〔_Μ〕相鄰的符號之間不會有⑻的現象,所以經過 解調出來的符號r(々)為: m = xik)H (k)+ I(k)+ w = (五) ^中剛為通道之頻率響應,猶發射機與接收機之 都卜勒效應所形成的W,_則為咖之傅利葉轉換。 在=式㈤中,我們經由通道估測咖)估測得到 通道之頻率響應剛後,再經由等化 控制(2_〔AGC〕得到原始之傳逆替w Μ自,, 到之接收訊號雄请 傳运訊號雄),因此最後得 (六) 响=蟲, 其中為估測得到的通道頻率響應。接收訊號/⑷ 再經由訊號反對應(290)還原成為原始之二位元資訊輸 出。 .請再一併參閱第二圖所示,為本發明之正交分頻多工 傳輸〔OFDM〕系統之估測架構流程圖,其步驟如下: (a) 發射訊號(371) —發射機第一個發射的符號為一已知 訊號,接收機(210)接收此已知符號即使用此已知訊 號進行通道估測(270)並儲存通道參數; (b) 錯誤偵測(372) —在接收資料符號時,接收機(210)可 利用發射機(170)發射所插入錯誤偵測訊號(130)執 行資料符號之錯誤偵測(250),偵測到符號有無錯誤 發生; (c) 執行通道估測(373)或不執行通道估測(375)_上述符 號表示為可靠符號,並使用此可靠符號進行通道估 測; (d) 更新通道參數(374)_藉由進行通道估測(27〇)以可更 新通道參數。 此通道估測法的實施例之一為當接收機(210)接收訊 號(241)經快迷傅利葉轉換(240)〔FFT〕後,需要進行通 道估測(270) ’以得到通道響應解回原訊號,我們在傳送 訊號的開頭先傳送一組全為領航訊號之正交分頻多工傳 輸〔OFDM〕符號用以估測未知的通道響應’為了降低估測 之誤差’首先’我們使用的最小均方誤差〔MMSE〕估測法, 正交分頻多工傳輪〔OFDM〕傳輸訊號開頭是一組全為領航 訊號如: pilot signal « = 0,1, 2, ...,#-1 (七) Ϊ352520 其使用之估測方法是先以最小平方〔LS〕估測法估算出通 道頻率響應; (八)r(k)=, DFT{y(n)}=±^y^ ~J2nbt / N moxibustion=0,1,1 (4) In the received signal, the error detection of the received signal (250) can be performed to detect Measure whether the received signal has an error. It is assumed that the length of the guard interval is greater than the length of the channel pulse (four)', so there is no (8) phenomenon between the adjacent symbols of the orthogonal splitter transmission [_Μ], so it is demodulated. The sign r(々) is: m = xik)H (k)+ I(k)+ w = (5) ^The frequency response of the channel is just formed by the Buhler effect of the transmitter and receiver. W, _ is the Fourier transform of the coffee. In the = (5), we estimate the frequency response of the channel through the channel estimation, and then pass the equalization control (2_[AGC] to get the original passback, and then receive the signal. The transmission signal is male), so the final (six) ring = worm, which is the estimated channel frequency response. The received signal/(4) is then restored to the original two-bit information output via the signal opposition (290). Please refer to the second figure again, which is a flowchart of the estimation architecture of the orthogonal frequency division multiplexing transmission (OFDM) system of the present invention, and the steps are as follows: (a) transmitting signal (371) - transmitter number A transmitted symbol is a known signal, and the receiver (210) receives the known symbol, uses the known signal for channel estimation (270) and stores channel parameters; (b) error detection (372) - at When receiving the data symbol, the receiver (210) may use the transmitter (170) to transmit the inserted error detection signal (130) to perform error detection (250) of the data symbol, and detect whether the symbol has an error; (c) Channel Estimation (373) or No Channel Estimation (375)_The above symbols are represented as reliable symbols and channel estimation is performed using this reliable symbol; (d) Update channel parameters (374)_by channel estimation ( 27〇) to update the channel parameters. One of the embodiments of the channel estimation method is that after the receiver (210) receives the signal (241) via the fast Fourier transform (240) [FFT], channel estimation (270) is required to obtain the channel response solution. Original signal, we transmit a set of orthogonal frequency division multiplexing (OFDM) symbols that are all pilot signals at the beginning of the transmission signal to estimate the unknown channel response 'in order to reduce the error of estimation'. First of all, we use The minimum mean square error [MMSE] estimation method, the orthogonal frequency division multiplexing transmission (OFDM) transmission signal starts with a set of all pilot signals such as: pilot signal « = 0,1, 2, ...,#- 1 (7) Ϊ352520 The estimation method used is to estimate the channel frequency response by the least square [LS] estimation method;
= XpY =-虛 Zfil 准-1) _功)A⑴ 4(#-1)= XpY =-virtual Zfil quasi-1) _work) A(1) 4(#-1)
其中冲)為接收到之訊號,而最小平方〔LS〕估測法 所估測出之通道響應為反;由於最小平方〔LS〕估測 法易受到雜訊(190)的干擾,所以在最小平方〔LS〕估測 法後再使用最小均方誤差〔MMSE〕估測法來進行更精確的 通道估測(270): ΛΗΡ, mmseThe rush is the received signal, and the channel response estimated by the least square [LS] estimation method is reversed; since the least square [LS] estimation method is susceptible to interference by the noise (190), it is at a minimum. The square [LS] estimation method then uses the minimum mean square error [MMSE] estimation method for more accurate channel estimation (270): ΛΗΡ, mmse
Rfffi RJ zj ntlP,LS nPJ^nPJSRfffi RJ zj ntlP, LS nPJ^nPJS
(九)(nine)
其中σ„2為雜訊(190) rfr)之變異數〔variance〕’其共 變異數矩陣為Where σ„2 is the variance of the noise (190) rfr), and the matrix of the common variance is
(十) 由方程式(九)可看出,只要傳送之領航訊號或訓練符 號八改變,就必須執行反矩陣的運算,最小均方誤差〔MMSE 〕估測法的複雜度也因此提高不少;可利用傳送符號的平 均值來降低最小均方誤差〔MMSE〕估測法的複雜度,於期 望值代替在方程式(九)中的(X〆/)-1,並假設在訊 號星座圖上,每一點訊號出現之機率是一樣的,因此得到 10 ¢352520 論文所提出之可靠符號通道估測法之效能比内插法好,當 在速度V=50 km/hr和V=100 km/hr時,我們同時發覺 可靠符號通道估測法因為通道變化較緩慢,因此可以容g 追縱到時變通道的變化,得到之BER值和在已知通道響應 下之BER結果接近,同時通道變化快速的環境中(速度16〇 km/hr),其效能表現也是可接受的。 而上述提出的發明實例僅為描述本發明正交分頻多 工傳輸〔0FDM〕之通道估測方法的原理及其功效,而非限 • 制本發明,故習於此技術人士欲於對上述實例進行修改與 變化,應在未脫離後述之申請專利範圍内。 在正父分頻多工傳輸〔0FDM〕系統中,對於通道估測 (270)的要求的是準確、資料率高和低複雜度之估測器, 本發明所提出之可靠符號估測法相較於c〇iQb_type蜇態的 領航訊號内插法,因為使用較少的子載波來傳送額外的資 訊,所以有較高的資料率。同時經由軟體模擬的結果,得 W可以號估測法在纟統效能表現上也比較好;在計算的 =雜度上’為了降低運算的複雜度我們使用奇異值分解來 估剩整個通道頻率響應。 综上所述,本發明實施例魏達到所預期之使用功 Φ ’又其所揭露之具體構造,不僅未曾見諸於同 類產品 ^亦未曾公開於中請前,誠已完全符合專利法之規定與 | ^ ’級法提出發明專利之巾請,料惠予審查,並賜 准專利,則實感德便。 14 1352520 錯誤偵測 更新通道參數 (371) 發射訊號 (372) (373) 執行通道估測 (374) (375) 不執行通道估測 16(10) It can be seen from equation (9) that as long as the transmitted pilot signal or training symbol is changed, the inverse matrix operation must be performed, and the complexity of the minimum mean square error [MMSE] estimation method is also improved. The average of the transmitted symbols can be used to reduce the complexity of the minimum mean square error [MMSE] estimation method, replacing the (X〆/)-1 in equation (9) with the expected value, and assuming that on the signal constellation, each The probability of a single signal is the same, so the reliable symbol channel estimation method proposed by 10 ¢ 352520 paper is better than the interpolation method. When the speed is V=50 km/hr and V=100 km/hr, we At the same time, it is found that the reliable symbol channel estimation method can track the change of the time-varying channel because of the slow change of the channel, and the BER value obtained is close to the BER result under the known channel response, and the channel changes rapidly. (speed 16 〇 km / hr), its performance is also acceptable. The above-mentioned invention examples are only for describing the principle and function of the channel estimation method of the orthogonal frequency division multiplexing transmission (OFDM) of the present invention, and are not limited to the invention, and therefore, those skilled in the art would like to Modifications and variations of the examples are intended to be within the scope of the appended claims. In the positive-father multiplexed transmission (0FDM) system, the estimator of the channel estimation (270) requires accurate, high data rate and low complexity, and the reliable symbol estimation method proposed by the present invention is compared. The pilot signal interpolation method in the c〇iQb_type state has a higher data rate because fewer subcarriers are used to transmit additional information. At the same time, through the results of software simulation, it is better to estimate the performance of the system. In the calculation of the noise, we use singular value decomposition to estimate the frequency response of the entire channel. . In summary, the embodiment of the present invention achieves the expected use of work Φ 'and the specific structure disclosed therein, not only has not been seen in the same product ^ and has not been disclosed before the middle of the request, Cheng has fully complied with the provisions of the Patent Law If the invention patent is issued with the | ^ ' level method, it is expected to be reviewed, and the patent will be granted. 14 1352520 Error Detection Update Channel Parameters (371) Transmit Signal (372) (373) Perform Channel Estimation (374) (375) Do not perform channel estimation 16
Claims (1)
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
TW96136267A TWI352520B (en) | 2007-09-28 | 2007-09-28 | Orthogonal frequency division multiplexing system |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
TW96136267A TWI352520B (en) | 2007-09-28 | 2007-09-28 | Orthogonal frequency division multiplexing system |
Publications (2)
Publication Number | Publication Date |
---|---|
TW200915751A TW200915751A (en) | 2009-04-01 |
TWI352520B true TWI352520B (en) | 2011-11-11 |
Family
ID=44725825
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
TW96136267A TWI352520B (en) | 2007-09-28 | 2007-09-28 | Orthogonal frequency division multiplexing system |
Country Status (1)
Country | Link |
---|---|
TW (1) | TWI352520B (en) |
Families Citing this family (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
TWI404360B (en) * | 2009-11-25 | 2013-08-01 | Inst Information Industry | Communication device adopted for multi-input multi-output orthogonal frequency division multiplexing system and method thereof |
CN102437976B (en) * | 2010-09-29 | 2014-09-10 | 中兴通讯股份有限公司 | Signal channel estimation method and base station |
CN110602006A (en) * | 2019-08-30 | 2019-12-20 | 深圳市海派通讯科技有限公司 | Channel estimation method under LTE system |
-
2007
- 2007-09-28 TW TW96136267A patent/TWI352520B/en not_active IP Right Cessation
Also Published As
Publication number | Publication date |
---|---|
TW200915751A (en) | 2009-04-01 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
JP5602773B2 (en) | Channel estimation for communication systems using spectral estimation | |
US8537908B2 (en) | Pilot transmission and channel estimation for an OFDM system with excess delay spread | |
KR101098053B1 (en) | Noise estimation for wireless communication | |
TWI407719B (en) | A symbol time synchronization method for ofdm systems | |
CN101917359B (en) | For receiving reception equipment and the method for signal in a wireless communication system | |
CN107147483B (en) | A kind of SIM-OFDM system communicating method based on pilot frequency design modulation | |
JP2005057644A5 (en) | ||
TWI352520B (en) | Orthogonal frequency division multiplexing system | |
JP3594828B2 (en) | Multicarrier modulation signal demodulator | |
CN103825856B (en) | Single frequency and narrowband interference-resisting automatic modulation method and system | |
US8774330B2 (en) | Coarse timing acquisition | |
JP6001806B2 (en) | Method and apparatus for transmitting multi-carrier signals | |
CN105052231B (en) | Receiving device in wireless communication system and channel estimation control method | |
Zhang et al. | A new channel estimation algorithm for fast linear-time-varying channel in MIMO-OFDM systems | |
CN109842577B (en) | Channel quality determination method under high dynamic situation | |
WO2005048497A2 (en) | Method for estimating time varying channels in ofdm (orthogonal frequency division multiplex) multiple transmit antenna system | |
Hu et al. | Estimation of rapidly time-varying channels for OFDM systems | |
KR20200082408A (en) | Method and apparatus for efficient frequency offset estimation in ofdm system | |
Lin | Reliable symbol channel estimation for OFDM systems | |
KR20100059569A (en) | Apparatus and method for detecting time synchronization of ofdm system | |
Athanasios et al. | SNR estimation in frequency selective Rayleigh channel for HIPERLAN/2 transceiver | |
KR20100077972A (en) | Method for estimating and compensating channel and receiver using the same | |
Lee et al. | A robust OFDM receiver for DSRC systems | |
Lee et al. | Performances of the superimposition schemes for OFDM systems | |
Li et al. | Circular orthogonal sequences based channel estimation for MIMO SC-FDE systems |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
MM4A | Annulment or lapse of patent due to non-payment of fees |