TW200915751A - Orthogonal frequency division multiplexing system and its channel estimating appliance and method - Google Patents
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200915751 九、發明說明: 【發明所屬之技術領域】 本發明係有關於一種正交分頻多工傳輸系統之通道 估測裝置與方法’尤其是指一種以完善的通道估測裝置與 方法來追蹤通道的快速變化,以提昇系統效能的目的。 【先前技術】 按,正交分頻多工傳輸〔Orthogonal Frequency Division Multiplexing; OFDM〕系統在無線通訊中,已 有許多研究被提出。在行動通訊系統中,無線通道通常是 頻率選擇性〔frequency selective〕及時變〔time varying 〕的,雖然,正交分頻多工傳輸〔0FDM〕系統有很好對抗 頻率選擇衰落的能力,然而先決條件是接收端要有一 好的通道估測系統方能提昇系統的效能,尤其當系統處快 速時變的無線通道中,接收端更需要有一較佳的動態通道 估測機制來輔助解調出更正確之正交分頻多工傳輸〔〇削 〕訊號,得到更好的系統效能。 接續,在先前技術中,為了瞭解未知的通道特性,通 號I加人領航訊號或訓練訊號,領航訊號 疋接㈣已知的訊號資訊,所以在接收端可以藉由領航訊 號來進行通道估測得到通道特性之嘗4 時,為了增加傳輸之頻寬,領航訊號只使 工傳輸〔_〕之少數特定子載波間,通道估測=針對 這些子载波騎通道躲的估測’然後再彻這些 到的子載波資訊對其⑽領航錢的子載波崎通道特 性估測,所使用之方法多為内插法。 、 然而,在先前技術中,很多正交分頻多工傳輸〔麵 200915751 〕系統之通道估測方法都是在假設為慢速衰落通道之情況 下被發展,這些系統通常假設通道在幾個正交分頻多工傳 輸〔0FDM〕符號時間内的變化量不大,因此在第一次的通 道估測後〔通常使用訓練符號來進行通道估測〕,到不次 的訓練符號前皆可使用先前所估測之通道特性來進行料 偵測。實際上’在寬頻無線通道中,通道是有可能在一個 正交分頻多工傳輸〔0FDM〕的符號内有明顯的變化,因此, 前後兩個符號所經過的通道特性會有差異,使用先前估測 得到的通道來進行下一個符號的資料偵測,有時候會產極 大的誤差,使得接收系統的效能降低,所以需要有更好之 通道估測方法才能在快速變化通道環境中得到更好的系 統效能。 有鑑於此,本發明人根據先前的技術加以研發提出正 交分頻多工傳輸系統之通道估測方法來達到提高接收效 率與降低偵測誤差的目的,以改善原本現有正交分頻多工 傳輸〔0FDM〕的缺失者。 【發明内容】 為了達到上述目的,本發明之正交分頻多工傳輸系統 之通道估測方法係由以下技術實現: 主要係以傳送端傳送子載波之錯誤偵測訊號,再經由 檢查接收端之接收訊號的正確與否來加強資料之正確 性,並決疋疋否需執行通道估測;藉由上述的通道估測方 法,玎以在快速的時變通道中得到較佳的系統效能者。 【實施方式】 為令本發明所運用之技術内容、發明目的及其達成之 功效有更疋整且清楚的揭露,茲於下面之實施例中詳細說 200915751 明之: 首先,請參閱第一圖所示,為本發明之正交分頻多工 傳輸〔0FDM〕系統之方塊圖,其主要係以傳送端將二位元 之資訊資料經過調變即訊號對應(110)後,經由串列轉並 列(120)成為串列資料後,再插入錯誤偵測訊號(130)〔 error detection〕’ 成為在頻域上〔freqUenCy domain〕 的調變子載波訊號iW,此錯誤訊號可用來偵測接收訊號 之錯誤’此調變訊號尤⑻再經由快速反傅利葉轉換(140) 〔IFFT〕將頻域的訊號义⑻轉換為時域訊號(141)〔 time domain ] χ(η): χ(η) = IDFT{x{k)}=Y^x(k)ej2idmlN ^ λ=0 π = 0,1,··.,#_ΐ (一) 其中水為正交分頻多工傳輸〔OFDM〕系統之子載波 個數。 為了防止接收號之符號間的干擾〔inter-Symb〇l interference〕現象發生,通常在兩個時域訊號之符號間 插入防護區間(15〇),成為正交分頻多工傳輸〔OFDM〕系 統之傳輸訊號(151)χ>):200915751 IX. Description of the invention: [Technical field of invention] The present invention relates to a channel estimation apparatus and method for an orthogonal frequency division multiplexing transmission system, in particular, a tracking device and method with perfect channel estimation Rapid changes in the channel to enhance system performance. [Prior Art] According to the Orthogonal Frequency Division Multiplexing (OFDM) system, many studies have been proposed in wireless communication. In mobile communication systems, the wireless channel is usually frequency selective and time varying. Although the orthogonal frequency division multiplexing (OFDM) system has good ability to resist frequency selective fading, the prerequisite is The condition is that the receiver must have a good channel estimation system to improve the performance of the system. Especially when the system is in a fast time-varying wireless channel, the receiver needs a better dynamic channel estimation mechanism to assist in demodulation. Correct orthogonal frequency division multiplexing transmission (boring) signals for better system performance. In the prior art, in order to understand the unknown channel characteristics, the number I adds a pilot signal or a training signal, and the pilot signal connects (4) the known signal information, so the channel can be estimated by the pilot signal at the receiving end. When the channel characteristics are tasted 4, in order to increase the bandwidth of the transmission, the pilot signal only transmits (_) between a few specific subcarriers, channel estimation = estimation of the channel hiding for these subcarriers, and then The subcarrier information obtained is estimated by the (10) pilot carrier channel characteristics of the pilot money, and the methods used are mostly interpolation. However, in the prior art, many channel estimation methods for orthogonal frequency division multiplexing transmission (200915751) systems are developed under the assumption of slow fading channels, which usually assume that the channel is in several positive The amount of change in the cross-frequency multiplex transmission (0FDM) symbol time is not large, so after the first channel estimation (usually using the training symbol for channel estimation), it can be used until the training symbol is not used. The channel characteristics previously estimated are used for material detection. In fact, in a wideband wireless channel, the channel is likely to have a significant change in the sign of an orthogonal frequency division multiplexing (OFDM). Therefore, the channel characteristics of the two symbols before and after the difference will be different. The estimated channel is used for data detection of the next symbol, sometimes producing a large error, which reduces the performance of the receiving system, so a better channel estimation method is needed to get better in the fast changing channel environment. System performance. In view of this, the inventors have developed a channel estimation method for orthogonal frequency division multiplexing transmission system according to the prior art to achieve the purpose of improving reception efficiency and reducing detection error, so as to improve the existing orthogonal frequency division multiplexing. The missing of the transmission [0FDM]. SUMMARY OF THE INVENTION In order to achieve the above object, the channel estimation method of the orthogonal frequency division multiplexing transmission system of the present invention is implemented by the following technologies: Mainly, the error detection signal of the subcarrier is transmitted by the transmitting end, and then the receiving end is checked. Whether the received signal is correct or not to enhance the correctness of the data, and whether it is necessary to perform channel estimation; by the above channel estimation method, the system performance is better in a fast time-varying channel. . [Embodiment] In order to make the technical content, the object of the invention and the effects thereof achieved by the present invention more comprehensive and clear disclosure, in the following embodiments, the details of 200915751 are as follows: First, please refer to the first figure. The block diagram of the orthogonal frequency division multiplexing transmission (OFDM) system of the present invention is mainly characterized in that the information of the two bits is modulated by the transmitting end, that is, the signal corresponding to (110), and then juxtaposed by serial transmission. (120) After becoming the serial data, insert the error detection signal (130) [error detection] to become the modulated subcarrier signal iW in the frequency domain [freqUenCy domain], and the error signal can be used to detect the received signal. Error 'This tuning signal (8) then converts the frequency domain signal (8) into a time domain signal (141) via the fast inverse Fourier transform (140) [IFFT] [ time domain ] χ(η): χ(η) = IDFT {x{k)}=Y^x(k)ej2idmlN ^ λ=0 π = 0,1,··.,#_ΐ (1) where water is the subcarrier of the orthogonal frequency division multiplexing (OFDM) system number. In order to prevent the interference (inter-Symb〇l interference) between the symbols of the receiving number, a guard interval (15〇) is usually inserted between the symbols of the two time domain signals to become an orthogonal frequency division multiplexing (OFDM) system. Transmission signal (151) χ >):
X x(N + n\ n = -Ng)X x(N + n\ n = -Ng)
Anl « = 0, 其中 义為插入防護區間(150)的長度。 插入防護區間(150)的時域訊號經由並列轉串列(16〇) 後,經過發射機(17〇)發射後通過無線通道(180)到接收機 (210) ’接收機接收到的訊號可表示: 200915751 ^(w)= h(n)+ w(n) (三) 其中為通道的脈衝響應,而w(«)則是可加性之Anl « = 0, where the meaning is the length of the insertion guard interval (150). The time domain signal inserted into the guard interval (150) is transmitted through the transmitter (17〇) and then transmitted through the wireless channel (180) to the receiver (210). The receiver receives the signal through the parallel transmission (16〇). Representation: 200915751 ^(w)= h(n)+ w(n) (iii) where is the impulse response of the channel, and w(«) is additivity
尚斯白雜訊(190)〔 Additive White Gaussian Noise, AWGN 〕’ ®為兩個訊號之旋積(conv〇lution)符號。 在接收端之解調步驟是,經過_列轉並列(220)後先 把移除防護區間(230),然後經過快速傅利葉轉換(240)〔 IFFT〕將時域上轉換到頻域上’成為頻域之接收訊號(241) Y(k) · ]2π]ίη/Ν ^ η=0 ^ = 〇, 1,··· ,Ν-l (四) 在接收訊號呛)中可以執行接收訊號之錯誤偵測 25〇),以偵測所接收之訊號是否有錯誤,假設防護區間 的長度大於通道脈_應的長度,因此正交分頻多工傳輸 〇随〕相鄰的符號之間不會有ISI的現象,所以經過 解調出來的符號呛)為:Additive White Gaussian Noise (AWGN)' ® is the conv〇lution symbol of two signals. The demodulation step at the receiving end is to remove the guard interval (230) after the parallel column (220), and then up-convert the time domain to the frequency domain through fast Fourier transform (240) [IFFT]. Frequency domain receiving signal (241) Y(k) · ]2π]ίη/Ν ^ η=0 ^ = 〇, 1,··· , Ν-l (4) The receiving signal can be executed in the receiving signal 呛) Error detection 25〇) to detect whether the received signal has an error, assuming that the length of the guard interval is greater than the length of the channel pulse, so the orthogonal frequency division multiplexing transmission will not follow the adjacent symbols. There is a phenomenon of ISI, so the demodulated symbol 呛) is:
Hk)= X(k)H(k)+ I(k)+w(k), k = 0,l,^,N-l (五: # ι 1、中^⑹為通道之頻率響應,价)為發射機與接收機之 都卜勒=應所形成的似,_則為咖之傅利葉轉換。 1、.在方程式(五)中,我們經由通道估測(270)估測得至 ^道之頻率響應鄉)後,再經由等化器(28GA)或自動增蓋 =制(28Gy AGC〕得到原始之傳送,因此最後_ 到之接收訊號尤⑹為 1 (六) 200915751 其中圮⑹為估測得到的通道頻率響應。接收訊號尤⑻ 再經由訊號反對應⑽)還原成為原始之二位元資訊輸 出。 明再-併參閱第二圖所示,為本發明之正交分頻多工 傳輸〔_M〕系統之估測架構流程圖,其步驟如下: (a)發射訊號(371)-發射機第—個發射的符號為一已知Hk)= X(k)H(k)+ I(k)+w(k), k = 0,l,^,Nl (five: # ι 1, middle ^(6) is the frequency response of the channel, the price is Both the transmitter and the receiver are similar to each other, and _ is the Fourier transform of the coffee. 1. In equation (5), we estimate the frequency response of the channel by channel estimation (270), and then obtain it by equalizer (28GA) or automatic cover = (28Gy AGC). The original transmission, so the last _ to receive the signal (6) is 1 (six) 200915751 where 圮 (6) is the estimated channel frequency response. The receiving signal (8) is then restored to the original two-bit information by the signal opposition (10) Output. Ming-- and referring to the second figure, the flow chart of the estimation architecture of the orthogonal frequency division multiplexing transmission [_M] system of the present invention is as follows: (a) transmitting signal (371) - transmitter - The transmitted symbol is a known
訊號’接收機(21G)接收此已知符號即使用此已知訊 號進行通道估測(270)並儲在福省灸貉. ⑹錯誤❹K372)-在接”料符^,接收機⑽)可 ,用發射機(17G)發射所插人錯誤制訊號⑴〇)執 仃貝料符號之錯誤债測(25〇),横測到符號有無錯誤 發生; (c)執行通道估測(373)或不執行通道估測(375)—上述符 號表示為可靠符號,並使用此可靠符號進行通道估 測; ⑷更新通道參數⑽)—藉由進行通道估測⑽)以可更 新通道參數。 此通道估測法的實施例之—為當接收機(21())接收訊 號⑽)經快速傅㈣轉換⑽)〔fft〕m進行通 道估測(27G) ’以得到通道響應解回原訊號,我們在傳送 訊號的開頭先傳送-組全為㈣訊號之正交分頻多 輸〔0FDM〕符號用以估測未知的通道響應,為了 之誤差,首先,我們使用的最小均方誤差/ 正交分頻多工傳輸〔咖〕傳輸訊號開頭是—組全為^ ’ 訊號如: 勺嗔航 (七)The signal 'receiver' (21G) receives this known symbol and uses this known signal for channel estimation (270) and stores it in Fuzhou Moxibustion. (6) Error ❹ K372) - In the "Material ^, Receiver (10)), use Transmitter (17G) transmits the error signal (1) 所) the wrong debt test (25〇) of the beet symbol, cross-measures whether the symbol has an error; (c) performs channel estimation (373) or does not execute Channel Estimation (375)—The above symbols are represented as reliable symbols and channel estimates are made using this reliable symbol; (4) Channel parameters (10) are updated—by channel estimation (10)) the channel parameters can be updated. In the embodiment, when the receiver (21()) receives the signal (10), the channel is estimated by the fast (four) conversion (10)) [fft]m (27G) 'to get the channel response to return the original signal, we are transmitting the signal The beginning of the transmission - the group is all (four) signal orthogonal frequency division multiple input [0FDM] symbol to estimate the unknown channel response, for the error, first, we use the minimum mean square error / orthogonal frequency division multiplexing The transmission [coffee] transmission signal starts with - the group is all ^ ’ Signals such as: Scoop voyage (7)
Xp(^hpilot signal neQD,…,N~1 9 200915751 其使用之估測方法是先以最小平方〔LS〕估測法估算出通 道頻率響應; =[^,ω(〇) ^/>,ω⑴··. ι)]Γ = Χ;!7 —「r(o) r(i) 冲) 咖-i) 丫 其中r(〇為接收到之訊號,而最小平方〔LS〕估測法 所估測出之通道響應為也由於最小平方〔LS〕估測 法易受到雜訊(190)的干擾,所以在最小平方〔Ls〕估測 法後再使用最小均方誤差〔MMSE〕估測法來進行更精確的 通道估測(270):Xp(^hpilot signal neQD,...,N~1 9 200915751 The estimation method used is to estimate the channel frequency response by least square [LS] estimation method; =[^,ω(〇) ^/>, Ω(1)··. ι)]Γ = Χ;!7 —“r(o) r(i) 冲) coffee-i) 丫 where r(〇 is the received signal, and the least square [LS] estimation method The estimated channel response is also due to the least square [LS] estimation method susceptible to noise (190) interference, so the least squares error [MMSE] estimation method is used after the least square [Ls] estimation method. For more accurate channel estimation (270):
其中 <為雜訊(190)rW之變異數〔variance〕,其丘 變異數矩陣為 八八Where < is the variance of the noise (190) rW, and its mound coefficient matrix is eight or eight
由方私式(九)可看出,只要傳送之領y 號八改變’就必須執行反矩陣的運算,最小 〕估測法的複雜度也因此提高不少; 運算’最小均方誤差〔MMSE ‘少;可利用值找炫號的平It can be seen from the private (9) that as long as the transmission of the y number eight changes 'there must be the operation of the inverse matrix, the minimum] the complexity of the estimation method is also improved a lot; the operation 'minimum mean square error MMSE 'Less; can use the value to find the flat
现生座圖上’每—職號出現之機率是-樣的 现生座圖上, 只要傳送之領航訊號或訓練符 ,於期 ΙΓ>ν設在訊 ,因此得到 tQr ή. 10 200915751 =邱〜⑷| / ’其中I為單位矩陣,同時根據 (signal-to-noise ratio )的定義咏〆作γ,將方程式 (九)簡化成為 \-ι 食p=Rhh反冊― βOn the live seat map, the probability of occurrence of each job number is on the current seat map. As long as the pilot signal or training symbol is transmitted, the time ΙΓ > ν is set in the news, so get tQr ή. 10 200915751 = Qiu ~(4)| / ' where I is the identity matrix, and γ is defined according to the definition of (signal-to-noise ratio), and equation (9) is simplified as \-ι 食 p=Rhh
lP,LS (十一) 其中Θ = ♦(〇邱~(*)|為一常數,其值取決於訊號星座 圖對於16-QAM系統之々值為一⑺9。如果及册和snr在 —開始時為已知的,因此只需要計算一次々册|^册既 可。雖然(十一)式可以避免重覆之反矩陣的運算,^對於 2測器的整體而&,其複雜度還是相當高。因為通道相關 =(channel correlation matrix) Λ册需要 Ν 次的複 、」法運算,為降低乘法運算的次數,提出奇異矩陣分解 ,异法〔SVD〕分解將通道相關矩陣分解為 (十二) fe …1 μ0,μι,..·,《λμ,Λ為對 皁(dia-g〇nal matrix ),其對角元音為 ^離._婦-細。如此可得到一低複雜度之估測方程式lP, LS (11) where Θ = ♦ (〇邱~(*)| is a constant whose value depends on the value of the signal constellation for the 16-QAM system is one (7) 9. If the book and snr are at - start The time is known, so it only needs to be calculated once. ^^ The volume can be avoided. Although (11) can avoid the operation of the repeated inverse matrix, ^ is the overall complexity of the 2 detector, and its complexity is still It is quite high. Because the channel correlation matrix (reporting matrix) requires a complex, "method operation", in order to reduce the number of multiplication operations, a singular matrix decomposition is proposed, and the heterogeneous [SVD] decomposition decomposes the channel correlation matrix into (10). b) fe ...1 μ0, μι,..·, "λμ, dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia dia Estimation equation
SNR ^HH ~ UAXJ 其中U為行正交矩陣,其行向量為SNR ^HH ~ UAXJ where U is a row orthogonal matrix and its row vector is
HP=UHP=U
UhHUhH
PyLS (十三) 其中~是一對角矩陣,其内容為 ,众=0,1,·..,# —1PyLS (13) where ~ is a pair of angular matrices, the content of which is , public = 0,1,·..,#-1
雄)=iW X(k)+~^~ SNR (十四 通道估測法之工作方塊圖係如第三圖所示。 月再併參閱第四圖所示,為本發明之正交分頻多 工 200915751 2輸〔OFDM〕系統之可靠符號通 Γ=7增广通道估測(27°)時資=== (CheCkSUn〇 載波中傳送整個符號之加總和 CLhecksuni)值,因為傳送加總和值之 u和 μ 可得到較大的資料頻寬 在接收端,針對領航符號進第—次之通道⑺’ 面之資料則依然此估測之通道 U 270 ),後 之符號包含有加總和之訊息,在接收 =之:是否正確’如果資料經由加總和的 確無誤貝j表不此-符號為可靠的符號,因此 利用此一符號進行一般通道估測( 270 ),在此我 聰E通道估測法,用以得到現在之通道參 ( 270)㈣上—個估測之通道參數給下—個接 用,直到接收到正確的符號時再重新估測通道;如此町 以不需每個正交分頻多工傳輸〔〇FDM〕符號都作通道估測 (270)的動作,也可以追蹤時變通道的變化,同時系效 能也可以提高〔請一併參閱第五圖所示〕。 、、> 以下為本發明正交分頻多工傳輸系統之通道估測方 法所作之模擬驗證,首先,我們將設定正交分頻多工傳輸 〔OFDM〕的模擬參數,正交分頻多工傳輸〔〇FDM〕系統之 調變使用16-QAM,而載波之中心頻率為2.4GHz,頻寬為 20MHz ’子載波的總數為n=64個,其中61個子栽波傳送 一般資料’另外3個子載波傳送check sum訊說;無綠 通道模型為Jakes’ model之時變多路徑通道;假設防^ 區間(Guard intervals)大於通道之最大的路徑延遲,亦 12 200915751 即此系統沒有ISI的現象,接下來針對時變通道在速度不 同的情況下’利用不同的通道估測法來估測通道 ,並且比 車父其效能好壞’當在傳送端時’ 一個正交分頻多工傳輸〔 0FDM〕符號中均勻的插入領航訊號,在接收 針對 航訊號估測其通道頻轉,再通過_法計算出完整的通 道,模擬中的内插領航訊號個數為1M倍原訊號,可看 出内插法與che-ck sum的方法是截然不同的,所以我們 以MATLAB來模擬其效能的差別,模擬過程中,我們比較 估測值與真實值的通道響應之均方差(MSE),此均方差之 定義為Male)=iW X(k)+~^~ SNR (The working block diagram of the fourteen channel estimation method is shown in the third figure. See the fourth figure again, which is the orthogonal frequency division of the present invention. Multiplex 200915751 2 OFDM system reliable symbol overnight = 7 augmented channel estimation (27 °) time === (CheCkSUn 〇 carrier transmits the total sum of CLHecksuni), because the transfer sum value The u and μ can get a larger data bandwidth at the receiving end, and the data for the first-time channel (7) of the pilot symbol is still the estimated channel U 270), and the subsequent symbol contains the summed message. , in the reception = it is correct - if the data is correct through the sum of the sum of the words - the symbol is a reliable symbol, so use this symbol for general channel estimation (270), here I Cong E channel estimation The method is used to obtain the channel parameters of the current channel (270) and (4) for the next channel, and then re-estimate the channel until the correct symbol is received; The frequency division multiplexing transmission (〇FDM) symbol is used for the channel estimation (270) action, and can also Tracking changes in time-varying channels, while improving system performance (please refer to Figure 5). The following is the simulation verification of the channel estimation method of the orthogonal frequency division multiplexing transmission system of the present invention. First, we will set the analog parameters of the orthogonal frequency division multiplexing transmission (OFDM), and the orthogonal frequency division is more. The modulation of the transmission [〇FDM] system uses 16-QAM, and the center frequency of the carrier is 2.4 GHz, and the bandwidth is 20 MHz. The total number of subcarriers is n=64, of which 61 subcarriers transmit general data 'another 3 The subcarrier transmits a check sum message; the green channel model is a time-varying multipath channel of the Jakes' model; assuming that the Guard intervals are greater than the channel's maximum path delay, 12 200915751, the system has no ISI phenomenon. Next, the time-varying channel is used to estimate the channel using different channel estimation methods at different speeds, and it is better than the car's performance. When it is at the transmitting end, an orthogonal frequency division multiplexing transmission [0FDM] 〕 The symbol is evenly inserted into the pilot signal, and the channel frequency is estimated for receiving the navigation signal. Then, the complete channel is calculated by the _ method, and the number of the interpolation pilot signals in the simulation is 1M times the original signal. It can be seen that the interpolation method is completely different from the che-ck sum method, so we use MATLAB to simulate the difference in performance. During the simulation, we compare the mean square error (MSE) of the channel response between the estimated value and the true value. This mean square error is defined as
MSE 成|鄉)〜邱〗 (十五: 明-併參閱第六圖所示’為傳送四百個 傳輸〔_〕符號(一般一個傳送封包為綱〜個^多工 脱在通道有變彳日顧可#符號估測法之 蹤到時變通道的:^可以看出可靠符號估測法是可以笔 速度(V=5GWh/:; —併參㈣七圖所示,為比較在不同 的通道和實際通道^1〇〇1^與V=1嶋/hr)下, 可靠符號通道對娜的比較,由圖中可得知 出的方法較内插^之車交内插法低,表示我們所摘 不同速度下之b 請—併參閱第八圖所示,為MSE名 速度下之MSE =圖中顯示可靠符號估測之方法在不序 測能力上較㈣法低,麵可靠賴估測在通道仓 請一併參閱塗 160 km/hr時,二九圖所示,為移動速度在V,、1〇〇、 E“fSNR的效能比較’由圖中顯示出冰 13 200915751 論文所k出之可#符號通道估測法之效能比内插法好,當 在速度V=50 km/hr和V=i〇〇 km/hr時,我們同時發& 可靠符號通道估測法因為通道變化較緩慢,因此可以容易 追縱到時變通道的變化,得到之BER值和在已知通道響應 下之BER結果接近,同時通道變化快速的環境中(速度ι6〇 km/hr)’其效能表現也是可接受的。 而上述提出的發明實例僅為描述本發明正交分頻多 工傳輸〔0FDM〕之通道估測方法的原理及其功效,而非限 制本發明,故習於此技術人士欲於對上述實例進行修改與 變化,應在未脫離後述之申請專利範圍内。 在正父分頻多工傳輸〔0FDM〕系統中,對於通道估測 (270)的要求的是準確、資料率高和低複雜度之估測器, 本發月所出之可靠符號估測法相較於C型態的 領航讯號内插法,因為使用較少的子載波來傳送額外的資 甙,所,有較高的資料率。同時經由軟體模擬的結果,得 到可靠符號估測法在系統效能表現上也比較好;在計算的 ,雜度上,為了降低運算的複雜度我們使用奇異值分解來 估測整個通道頻率響應。 、’'τ'上所述,本發明實施例確能達到所預期之使用功 又其所揭露之具體構造,不僅未曾見諸於同類產品 亦未曾公’φ請前,誠e完全符合專利法之規定與 爰依法提出發明專利之巾請,懇請惠予審查,並賜 准專利,則實感德便。 14 200915751 圖式簡單說明】 第-圖:本發明系统之方塊圖 f二圖:本發明系統之通道估測法流程圖 第三圖隱通道估測法之工作方塊圖 =® 可靠符說通道估測法之工作方塊圖 f五圖:本發明之可靠符號估測法之流程圖 第六圖·本發明通道估測之MSE比較圖 第七圖:本發明㈣的通道和實際通道之MSE Cheng | Township ~ Qiu〗 (Fifteen: Ming - and refer to the figure shown in Figure 6 for the transmission of four hundred transmission [_] symbols (generally a transmission packet for the class ~ a ^ multi-work off in the channel has changed顾顾可# The symbolic estimation method traces to the time-varying channel: ^ It can be seen that the reliable symbol estimation method can be pen speed (V=5GWh/:; - and refers to (four) seven graphs, for comparison in different The channel and the actual channel ^1〇〇1^ and V=1嶋/hr), the comparison of the reliable symbol channel to Na, the method that can be known from the figure is lower than the interpolating method of the interpolated ^. We pick b at different speeds - and see the eighth picture, MSE = MSE = speed in the figure shows the method of reliable symbol estimation in the non-sequence test ability is lower than the (four) method, the surface is reliable In the channel warehouse, please refer to the coating 160 km / hr, shown in Figure XX, for the moving speed in V, 1, 〇〇, E "fSNR performance comparison" shown by the figure of ice 13 200915751 The efficiency of the ### channel estimation method is better than the interpolation method. When the speed is V=50 km/hr and V=i〇〇km/hr, we simultaneously send & reliable symbol pass Because the channel changes slowly, the estimation method can easily track the change of the time-varying channel, and the BER value is close to the BER result under the known channel response, and the channel changes quickly (speed ι6〇km/ Hr)' performance is also acceptable. The above-mentioned invention examples are only for describing the principle and function of the channel estimation method of the orthogonal frequency division multiplexing transmission (OFDM) of the present invention, and do not limit the present invention. Modifications and variations of the above examples are intended to be within the scope of the appended claims. In the Orthodox Crossover Multiplex Transmission (0FDM) system, the requirements for channel estimation (270) are required. It is an accurate, high data rate and low complexity estimator. The reliable symbol estimation method in this month is compared to the C-type pilot signal interpolation method because fewer subcarriers are used to transmit additional There is a high data rate, and at the same time, through the results of software simulation, the reliable symbol estimation method is also better in system performance; in computing, the complexity, in order to reduce the complexity of the operation We use singular value decomposition to estimate the frequency response of the entire channel. As described in ''τ', the embodiment of the present invention can achieve the expected use of the work and the specific structure disclosed, not only has not been seen in similar products. Before the public's request, Cheng e fully complied with the provisions of the Patent Law and the invention of the invention patent towel, please ask for the review, and grant the patent, then the real sense of virtue. 14 200915751 Simple description of the schema] Block diagram f of the system of the present invention: Flow chart of the channel estimation method of the system of the present invention. Figure 3: Working block diagram of the hidden channel estimation method =® Reliable character: The working block diagram of the channel estimation method f: Flow chart of the reliable symbol estimation method of the present invention. FIG. 6 is a comparison diagram of the MSE of the channel estimation of the present invention. FIG. 7 is a channel and an actual channel of the invention (IV).
MSE 對 SNRMSE vs SNR
的比較圖 第八圖.本發明在不同速度下,為·在不同速度下. 之比較圖 第九圖.本發明為移動速度下BERif SNR的效能比較 圖 【主要元件符號說明】 <本發明> (110) 訊號對應 (130) 插入錯誤偵測訊號 (141) 時域訊號 (151) 傳輪訊號 (170) 發射機 (190) 雜訊 (220) 串列轉並列 (240) 快速傅利葉轉換 (250) 錯誤偵測 (270) 通道估測 (280B) 自動增益控制 (120) 串列轉並列 (140) 快速反傅利葉轉換 (150) 插入防護區間 (160) 並列轉串列 (180) 無線通道 (210) 接收機 (230) 移除防護區間 (241) 接收訊號 (260) 並列轉串列 (280A) 等化器 (290) 訊號反對應Figure 8 is a comparison of the present invention at different speeds, at different speeds. Figure IX. The present invention is a comparison of the performance of BERif SNR at moving speed. [Main component symbol description] <The present invention > (110) Signal Correspondence (130) Insert Error Detection Signal (141) Time Domain Signal (151) Transmitter Signal (170) Transmitter (190) Noise (220) Tandem Rotation (240) Fast Fourier Transform (250) Error Detection (270) Channel Estimation (280B) Automatic Gain Control (120) Tandem Rotation (140) Fast Inverse Fourier Transform (150) Insertion Protection Interval (160) Parallel Array (180) Wireless Channel (210) Receiver (230) Remove guard interval (241) Receive signal (260) Parallel to serial (280A) Equalizer (290) Signal opposition
15 200915751 (371) 發射訊號 (372) (373) 執行通道估測 (374) (375) 不執行通道估測 錯誤偵測 更新通道參數 1615 200915751 (371) Transmit signal (372) (373) Perform channel estimation (374) (375) Do not perform channel estimation Error detection Update channel parameters 16
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TWI404360B (en) * | 2009-11-25 | 2013-08-01 | Inst Information Industry | Communication device adopted for multi-input multi-output orthogonal frequency division multiplexing system and method thereof |
CN110602006A (en) * | 2019-08-30 | 2019-12-20 | 深圳市海派通讯科技有限公司 | Channel estimation method under LTE system |
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TWI404360B (en) * | 2009-11-25 | 2013-08-01 | Inst Information Industry | Communication device adopted for multi-input multi-output orthogonal frequency division multiplexing system and method thereof |
WO2012041047A1 (en) * | 2010-09-29 | 2012-04-05 | 中兴通讯股份有限公司 | Channel estimation method and base station |
CN110602006A (en) * | 2019-08-30 | 2019-12-20 | 深圳市海派通讯科技有限公司 | Channel estimation method under LTE system |
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