1309915· 九、發明說明： • μ η丨喝〜仪w '明，j 本發明係關於一種軟性切換之 、 -種使超前橋臂、滯後橋臂均易 目式全橋電路，尤指 效解決輸出整流二極體反向恢復 見零電壓切換’且有 设問碭的移相式全橋電路。 【先前技術】1309915· Nine, invention description: • μ η丨 drink ~ instrument w 'ming, j This invention is about a kind of soft switching, - the kind of the front bridge arm and the lag bridge arm are easy to see the full-bridge circuit, especially the solution The output rectification diode reverse recovery sees zero voltage switching' and there is a phase-shifting full-bridge circuit with a problem. [Prior Art]
包括有 郊昂卞九圖所 —變壓器（7 0 ); -超前橋臂（7 1 ) ’係由兩電晶體M1、Μ2組成， •〜兩電晶冑Μ1、M2的連接節點係與變壓g ( 7 〇 ) 一次 #的—端連接； ^ —滯後橋臂（7 2 )，係由兩電晶體M3、M4組成， X兩電晶體M3、M4的連接節點係與變壓器（7 〇 ) 一次 φ 側的另端連接； 一諧振電感l_S，係串接於超前橋臂（7丄）中兩電晶 體Μ1、M2的連接節點與變壓器（7 〇 ) 一次侧之間； —輸出電路（7 3 )，係設於變壓器（7 0 )的二次 側上’主要由整流二極體D5、D6、輸出電感L5及輸出電 容c〇等組成。 前述超前橋臂（7 1)中的兩電晶體M1、M2與滯 橋臂（7 2 )的兩電晶體M3、M4均係以180度構成互 補導通’而超前橋臂（7 1 )與滯後撟臂（7 2 )的導通 4 1309915 是：差-個相&，故稱為移相式。而超前橋臂（7 "兩 電日日肢M1、M2的驅動信號係分別領先於滯後橋臂（7 2 )的兩電晶體M3、M4。 與傳統的全橋電路相較，前述的全橋電路在變壓器（ :) 一次側與超前橋臂（7 1 )兩電晶體M1、M2連接 即點間串接有一諧振電《Lse如是的設計可以使滯後橋臂 (7 2 )兩電晶體M3、M4在寬負載範圍實現零電壓切換 ’然而衍生的問題是因加入的諧振電《u損耗大，且使 :路的有效佔空比損失嚴重，另_ (7〇)二次側整 流二極體的反向恢復問題亦未獲得解決。 又如第一十圖所示，係又一種已知的移相式全橋電路 ’其基本架構與第十九圖大致㈣，不同處在於错振電感 係串接於變壓11 (7Q)二次側與整流二極體D5之門 ::種變型設計存在問題與第十九圖相同，都是加入電感 後扣耗大’且未解決整流二極體的反向恢復問題。 再如第二十一圖所，示，係再一種已知的移相式全橋電 路；其基本架構與第十九圖大致相同，不同處在於變壓器 (7 〇 ) —次側上增加了兩箝位二極體D7、D8。此種< 計雖可：效地降低繼（7〇)二次側上整流二極體： 復而產生的電壓尖峰，但該線路依然存在所加 才貝耗大、佔空比損失嚴重等問題，且變壓器（7 〇 : 側整流二極體的反向恢復亦未完全改善。 人 由^述可知，既有移相式全橋電路普遍存在加入★皆振 电感後線路⑽€變大且整流二極體反向恢復問題未獲完^ 1309915 改善等問題，除此以外，所述全橋電路的滯後橋臂（7 2 )電晶體M3、M4實現零電壓切換較為不易，原因在於電 晶體截止後，變塵器（7 〇 )二次側被短路，反射至…大 側之負載電流並未參與對電晶體M3、M4上寄生電容 、C4的充放電’僅僅依#變壓器（7Q) $漏電感中儲存 的能量’兩電晶體M3、M4即很難實現零電壓切換。由此 可見’既有全橋電路有待進—步檢討，並謀求可行的解決 方案。 【發明内容】 的在提供一種可有效降低線路損 ，且有效解決輸出整流二極體反 電路。 的主要技術手段係令前述移相式 因此，本發明主要目 耗、易於實現零電壓切換 向恢復問題的移相式全橋 為達成前述目的採取 全橋電路包括有： 一變壓器；Including the suburbs of the Angkor Nine Diagrams - Transformer (7 0); - The leading bridge arm (7 1 ) ' consists of two transistors M1, Μ 2, ~ ~ two crystal 胄Μ 1, M2 connection node and transformer g ( 7 〇) One-time connection of the #; ^—The lag bridge arm (7 2 ) consists of two transistors M3 and M4, the connection node of the X two transistors M3 and M4 and the transformer (7 〇) once φ side The other end of the connection; a resonant inductor l_S, connected in series between the two transistors Μ1, M2 in the leading bridge arm (7丄) and the transformer (7 〇) primary side; - output circuit (7 3), It is disposed on the secondary side of the transformer (70) and is mainly composed of rectifying diodes D5 and D6, an output inductor L5, and an output capacitor c〇. The two transistors M1 and M2 in the aforementioned leading arm (7 1) and the two transistors M3 and M4 of the bridge arm (72) form a complementary conduction at 180 degrees and the leading bridge arm (7 1 ) and hysteresis The conduction of the arm (7 2 ) 4 1309915 is: difference - phase &, so called phase shifting. And the front bridge arm (7 " two electric day, the limbs M1, M2 drive signal are respectively ahead of the two bridges M3, M4 of the lag bridge arm (72). Compared with the traditional full-bridge circuit, the aforementioned full The bridge circuit is connected to the two transistors M1 and M2 on the primary side of the transformer ( :) and the lead bridge arm (7 1 ), that is, a resonant connection is made between the points. Lse is designed to make the hysteresis bridge arm (7 2 ) two transistors M3 M4 achieves zero voltage switching over a wide load range' However, the problem is that the added resonant power "u loss is large, and the effective duty cycle loss of the circuit is severe, and another _ (7 〇) secondary side rectifying diode The problem of reverse recovery of the body has not been solved. As shown in the tenth figure, there is another known phase-shifted full-bridge circuit whose basic structure is substantially the same as that of the nineteenth figure. The difference lies in the vibration-damping inductance. It is connected in series with the secondary side of transformer 11 (7Q) and the gate of rectifier diode D5: There is a problem with the design of the variant, which is the same as that of the nineteenth figure, and the deduction is large after adding the inductor, and the rectifier diode is not solved. The reverse recovery problem of the body. As shown in Figure 21, there is another known phase-shifting full-bridge power. The basic structure is roughly the same as that of the nineteenth figure. The difference lies in the transformer (7 〇)—the two clamp diodes D7 and D8 are added on the secondary side. This kind of < 7〇) Rectifying diode on the secondary side: The voltage spike generated repeatedly, but the line still has problems such as high consumption of the added capacitance, serious duty cycle loss, and the transformer (7 〇: side rectifying diode) The reverse recovery has not been completely improved. It can be seen from the description that there is a phase shifting full-bridge circuit that is ubiquitously added. After the inductance is applied, the line (10) becomes larger and the reverse recovery of the rectifier diode is not completed. ^ 1309915 In addition to the improvement, the hysteresis bridge arm (72) of the full-bridge circuit realizes zero voltage switching, which is difficult because the transistor is turned off, and the secondary side of the dust collector (7 〇) Short-circuited, reflected to the large side of the load current does not participate in the parasitic capacitance on the transistors M3, M4, C4 charge and discharge 'only depends on # transformer (7Q) $ energy stored in the leakage inductance' two transistors M3, M4 That is, it is difficult to achieve zero voltage switching. It can be seen that 'there is a full bridge circuit It is necessary to further review and seek a feasible solution. [Invention] The main technical means for effectively reducing the line loss and effectively solving the output rectifying diode reverse circuit is to make the phase shifting type. The phase-shifting full bridge of the present invention, which is easy to realize zero-voltage switching to recovery problem, adopts a full-bridge circuit for achieving the foregoing purposes, including: a transformer;
一超刖橋臂，将A ’該兩電晶體的連接 ’該兩電晶體的連接 中兩電晶體的連接節 次側與阻斷電容之間 知由兩電晶體矣 節點係與變壓器—次伽& 人側的~端連老 一滯後橋臂，在a工 係由兩電晶體 節點係與變壓器-次側的另端連中 -阻斷電容’係串接於超前: 點與變壓器一次側之間. 一諧振電感，传由 係串接於變壓 6 1309915 電容與相連接的一 知透過電感與變壓 電感組成 器一次側 —輔助橋臂，係由至少— °亥電容—端與電源連接，另 連接； :出一 Ί 設於變壓器的二次側上，由至少兩整 在：輪出電感、一輸出電容等組成。 橋臂電設計中，係利用輔助橋臂儲存能量在滞後 實現零;:::後:Γ生電叫^ 變H 再者’由於阻斷電容的加入，除可防止 變壓斋偏磁外，Β产★ ΠΒ 际J丨万Jil 流二極體導通 開始階段提供-個電壓迫使一整 與错振電感開始諧振，使一；：電心=路’阻斷電容 流由-整济二先… 轉換負。而二次側電 ’轉移電流的整产-托M 一 纟轉移το成後 制變壓$ ^ ㈣貫現零電流切換，從而可有效抑 二 人側整流二極體的反向恢復問題。 月）述的辅助橋臂係由一 相互連接且跨接於電㈣上，兩電容係 與變壓器—次㈣接。、—者的連接節點透過電感 刖述諧振電感為—獨立電感元件。 :述諧振電感係利用變壓器的洩漏電感構成。 如述輸出電路為一全波整流電路。 則述輪出電路為一橋式整流器。 【實施方式】 如第—圖所示’揭示有本發明-較佳實施之詳細電路 1309915 圖，其包括有： 一變壓器（10)(圖中斿狀Np去 、固甲付唬NP為—次側之繞組匝 數，NS1、NS2為二次側繞組阻數，且n = NP/NS1 = NP/NS2); -超前橋臂⑴），係由兩電晶體MU組成， 該兩電晶It M1、M2的連接節點係與變壓器（ι〇) 一次 側的一端連接； 一滯後橋臂（1 2 )’係由兩電晶體M3、M4組成， 該兩電晶體M3、M4的連桩铲田ut 们連接即點係與變壓器（丄〇 側的另端連接； -阻斷電容係串接於超前橋 體M1、M2的連接節點與變屋器（1〇)—次j之中^電曰曰 一諧振電感Ls，係串接於變 斷電容C8之間； …（1〇) -次側與阻 -輔助橋臂（2 0 ) ’係由兩電容。6、及 ^組成，兩電容C6、C7係相 電感 ,運接且跨接於電源端Vin 上’兩電纟C6、C7的連接節點係 (1 〇 ) —次側連接； 電感L7與變壓器 -輪出電路（13)，係設於變 側上，主要由整流二極體D5、〇6 、）的二次 容C0等組成。 雨電感L5及輸出電 又如第二圖所示，係前述全橋 作週期内的理論波形，以下謹 件在-個工 各個㈣的工作原料-步說：：后橋電路在該遏期内 8 1309915 to〜t 1階段 月配〇參閱第三圖所標示的電流方向，在t〇之前，電 二組M1電晶體M3之本體二極體D3導通（iL7>jp)，電晶 體M3源茂極兩端的電壓箝位S 0V。在to時刻，電晶體 M3零電壓開通’此時施加在輔助橋臂（2 〇 )上電感L7 兩端的電壓Vac盔\/ir>/0 -. 為Vln/2，使IL7開始減小並反向增大，流 經電晶體Μ 3的雷、、* j _.. 曰]電抓id(M3广丨pHl7，變壓器（i 〇 ) 一次側 電流通過變壓哭r ! n、 k （ 1 〇 )、輸出電路（1 3 )的整流二極 體D5向負載傳遞功率。 t1〜t2階段 ^第四圖所TF °在t1時’電晶體M i在超前橋臂（丄 0)中兩電容C1、C2的作用下達成零電|關斷，此時反 射至變£裔（1 0 ) 一次側之電流丨〇/n與變壓器（1 〇 ) 的激磁電流開始共同對趙俞_始_ @ ^ ,、+ 剧橋臂（11)中的電容C1進 行充電’並對另一電容C2、# — -ίΑ·Λ5· - 电令進仃放電’而電晶體Μ1源洩 極兩端的電壓開始上升，堂s 電日日組Μ 2源洩極兩端的電壓（b 點電壓）開始下降。 t2〜t3階段 如第五圖所示。在„ T，電日日體Μ 1源浅極兩端的電 麗上升到V i η，電晶體μ t M2源洩極兩端的電壓下降到〇V， 同時箝位在0 V (忽略雷日雕Μ 0 电日日肢M2上本體二極體〇2的導通 壓降）’為電晶體M2零雷厭 令電Μ開通建立條件。從t2開始， 整流二極體D 5、D 6開栌拖、、* ^ _ Ί知換流’變壓器（1 0 )二次側被 短路’而切斷變壓器（1 , 丄U ) —次側反射到變壓器（1 〇 9 1309915 ) 久側的電感π2[_5，變壓, ,% a 趸氩窃（1 〇 )—次側電流iP在 vcs作用下’以Vcs/Ls的速率開始降低。 〜t4階段 如第六、七圖所示。在t3時，電晶體M2零電壓開通 ，變壓器變壓器（1 0 )二次側依然被短路，變壓器（工 0 ) —次側電流繼續以vC8/ls的速率下降並反向增大。 t4〜t5階段 如第八圖所示。在t4.時，變壓器（丄〇 ) 一次側電流 反向增大到丨o/η，流經整流二極體D5的電流減小到零並 開始反向增大，另一整流二極體D6的電流增大到丨〇 ;變 壓器（1 0 ) —次側電流下降率為Vc8/Ls，整流二極體 D5的電流下降率為（n/2)x(Vc8/Ls)，另一整流二極體〇6的 電流上升率為（n/2)x(VC8/Ls)。 在則揭先則技術中，第十九圖所示輸出電路（7 3 ) 的整流一極體D5、D6各別的電流下降率與上升率為（η/?) x(Vin/Ls) ’而Vin » VC8，致使整流二極體d5的反向恢復 和相對應之負面效應較強’透過本發明之改良設計，輸出 電路（1 3 )中整流二極體D 5的電流下降率已降低，其 意味著反向恢復效應已得到有效的抑制。 t5~t6階段 如第九圖所示。在t5時，流經整流二極體D5的反向 恢復電流達到最大值並開始迅速下降，整流二極體D 5開 始恢復阻斷，其電流下降率di/dt，並在線路中的寄生電感 (一般感量較小）上產生一個電壓尖峰，此電壓尖峰與2χ 1309915 (▽cs/n)相疊加，形成整流二極體〇5的反向電壓。在此時 ^線路中的電流流向與t4〜t5階段完全一致，只是變壓 °° 0 )—次側電流從峰值迅速回落，最後達到丨o/n， 從而整流二極體D5與D6換流結束。 在前揭先前技術中的第十九圖所示，因整流二極體D5 的電μ下降率較高’所產生的電壓尖峰也較高，此電壓尖 峰再與2x(Vjn/n)(非2x(Vc8/n))相疊加，致使整流二極 體D5的反向電壓較高。而經過本發明提出的技術方案， 輸出電路（13)中整流二極體D5 #電壓應力已顯著降 低而獲得改善。 〜t7階段 如第十圖所示。t6時，滞後橋臂（丄2 )電晶體M3 在滯後橋臂（1 2 )之電容〇3、C4作用下達成零電壓關 斷，此時電流（iLHP)開始對電容C3進行充電、對電容 C4進行放電，電晶體M3源茂極兩端的電壓（c點電壓） 開始上升，電晶體M4源洩極兩端的電壓開始下降。 t7〜t8階段 如第十一圖所示。t7時，電晶豸M3㈣極兩端的電 £上升到Vin，電體M4源洩極兩端的電壓下降到〇▽， 同時箝位在ον (忽略電晶體M4本體二極體D4的導通屙 降）’為電Μ M4零電襲通建立條件；儲存在輔助^ 臂（2 0 )電感L7中的能量開始通過電晶體Μ4本體二極 體D4回饋至輸入電源、Vin，流經電晶體μ…二：邮 D 4的電流為（i L 7 - i ρ )。 1309915 ιο从傻 如第十二圖所示，t8日夺，電晶體Μ4纟電塵開通，流 經電晶體Μ4的電流依然為（iLHp)，丨·口在^二vjn/2 的作用下開始減小並反向增大，當丨〔7下降到小於…時， 流經電晶體M4的電流正向上升，此後電路進入下半週期 之工作過程。由於下半週期的工作過程與上半週期類似， 故不再詳述。 、由上述說明可瞭解本發明一較佳實施例之具體電路構 造及其詳細的工作原理，而經進—步歸納本發明之特 如下列： .超前橋臂（11)之電晶體_、，實現零電壓切換 .在電晶體關斷後，由於有反射至變壓器（1 0 )—次側 載電/,“lo/n’丨〇為負載電流)參與對電晶體Mi、M2的 寄生電容：1、。進行充放電’對於電晶體M1、M2而言 本優勢。 電£切換，此為移相全橋電路之基 滯後橋臂（1 9 1 a & :在電晶體M3、M4 ^晶1" M3、M4實現零電壓切換 4Γ # 關斷後，因變壓器（1 0 )二次側被 紐路，反射至-次側 、丄U ;人側被 的寄生電I C3、C4未能對電晶體M3' M4 )漏感中儲存的能量订充放電，單純利用變壓器（1 0 切換。本發明經由增力：難使電晶體M3、，實現零電壓 (2 0 )中電容心、"助橋臂（2 0 )，利用輔助橋臂 M3、M4的寄生電办^、電感L7提供的電流，對電晶體 C3、C4進行充放電，因而可以實現 12 1309915 電晶體M3、M4的零電壓切換。。A super-bridge arm connects A 'the connection of the two transistors'. The connection between the two-transistor side of the two transistors and the blocking capacitor is known by the two transistors, the node and the transformer. & human side ~ end of the old one lag bridge arm, in the a work system from the two transistor node system and the transformer - the other side of the secondary side - blocking capacitor 'series in series: point and transformer primary side A resonant inductor, connected by a series of transformers 6 1309915 capacitor and phase connected through the inductor and transformer inductors of the primary side - auxiliary bridge arm, at least - ° capacitance - end connected to the power supply , another connection; : one set on the secondary side of the transformer, consisting of at least two in: the wheel inductance, an output capacitor and so on. In the design of the bridge arm, the auxiliary bridge arm is used to store energy in the lag to achieve zero;::: after: the electric generation is called ^ change H and then 'because of the addition of the blocking capacitor, in addition to preventing the deformation of the magnetic field , Β ★ ΠΒ 丨 J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J J ... convert negative. The secondary side of the 'transfer current' of the whole production - support M - 纟 transfer το into the post-variable voltage $ ^ (four) continuous zero current switching, which can effectively suppress the reverse recovery of the two-side rectifier diode. The auxiliary bridge arms described in the month are connected to each other and connected to the electric (four), and the two capacitors are connected to the transformer (fourth). The connection node of the person is transmitted through the inductance to describe the resonant inductance as an independent inductance component. The resonant inductor is constructed using the leakage inductance of the transformer. The output circuit is a full-wave rectifier circuit. The wheel circuit is a bridge rectifier. [Embodiment] As shown in the first figure, a detailed circuit 1309915 diagram of the present invention-best implementation is disclosed, which includes: a transformer (10) (in the figure, the Np is removed, the fixed NP is _ The winding turns on the side, NS1, NS2 are the secondary winding resistance, and n = NP/NS1 = NP/NS2); - The leading bridge arm (1)) is composed of two transistors MU, the two crystals It M1 The connection node of M2 is connected to one end of the primary side of the transformer (ι〇); the one of the lag bridge arms (1 2 )' is composed of two transistors M3 and M4, and the slabs of the two transistors M3 and M4 are connected. They are connected to the point system and the transformer (the other end of the 丄〇 side is connected; - the blocking capacitor is connected in series with the connecting node of the leading bridge body M1, M2 and the transformer (1 〇) - the second j ^ 曰曰A resonant inductor Ls is connected in series between the breaking capacitor C8; ...(1〇) - the secondary side and the blocking-auxiliary bridge arm (20) are composed of two capacitors, 6, and ^, and two capacitors C6 , C7 phase inductor, connected and connected across the power supply terminal Vin's two nodes C1, C7 connection node (1 〇) - secondary connection; inductor L7 and transformer - wheel circuit (13), system to On the variable side, it is mainly composed of the secondary capacitance C0 of the rectifying diodes D5, 〇6, and the like. The rain inductor L5 and the output power are as shown in the second figure, which is the theoretical waveform in the above-mentioned full bridge cycle. The following is the working material of each (four) work step - step:: the rear axle circuit is in the stoppage period 8 1309915 to~t 1 phase matching See the direction of current indicated in the third figure. Before t〇, the body diode D3 of the electric M1 transistor M3 is turned on (iL7>jp), the transistor M3 source The voltage across the poles clamps S 0V. At time to, the transistor M3 is turned on at zero voltage. At this time, the voltage across the inductor L7 on the auxiliary bridge arm (2 〇), Vac helmet \/ir>/0 -. is Vln/2, so that IL7 starts to decrease and reverse To increase, the lightning flowing through the transistor Μ 3, * j _.. 曰] electric catch id (M3 wide 丨 pHl7, transformer (i 〇) primary side current through the pressure to cry r! n, k (1 〇 ), the rectifying diode D5 of the output circuit (1 3 ) transmits power to the load. t1~t2 stage ^ fourth figure TF ° at t1 'the transistor M i in the leading bridge arm (丄0) two capacitors C1 Under the action of C2, zero electricity is turned off | Shutdown, at this time, the reflection is changed to the Japanese (1 0). The current of the primary side 丨〇/n and the excitation current of the transformer (1 〇) begin to work together on Zhao Yu _ _ @ ^ , and the capacitor C1 in the bridge arm (11) is charged 'and the other capacitor C2, # _ Α Α · · · · · · 而 而 而 而 而 而 而 而 而 而 而 而 电 电 电 电 电 电 电 电 电 电 电 电 电 电 电 电 电 电 电The temperature of the two ends of the source drain (b point voltage) begins to decrease. The stage of t2~t3 is as shown in the fifth figure. In „T, the electric day and the day Μ1 Rise to V i η, The voltage at both ends of the crystal μ t M2 source drops to 〇V, and the clamp is at 0 V (ignoring the conduction voltage drop of the body diode 〇2 on the Japanese limb M2 on the electric day). The zero-throwing anger makes the electric smash open and establishes the condition. Starting from t2, the rectifying diodes D 5 and D 6 are opened and dragged, and * ^ _ Ί knows that the commutator 'transformer (1 0) is short-circuited on the secondary side' Transformer (1, 丄U)—the secondary side is reflected to the transformer (1 〇9 1309915). The inductance of the long side is π2 [_5, variable voltage, % a 趸 argon stealing (1 〇)—the secondary current iP is under the action of vcs' At the rate of Vcs/Ls, the voltage starts to decrease. The stage of ~t4 is shown in the sixth and seventh diagrams. At t3, the zero voltage of the transistor M2 is turned on, and the secondary side of the transformer transformer (10) is still short-circuited, and the transformer (work 0) - The secondary current continues to decrease at the rate of vC8/ls and increases in the reverse direction. The stage t4~t5 is shown in Figure 8. At t4., the transformer (丄〇) primary side current is reversed to 丨o/ η, the current flowing through the rectifying diode D5 is reduced to zero and starts to increase in the opposite direction, and the current of the other rectifying diode D6 is increased to 丨〇; the transformer (10)-the secondary side The current drop rate is Vc8/Ls, the current drop rate of the rectifying diode D5 is (n/2)x (Vc8/Ls), and the current rising rate of the other rectifying diode 〇6 is (n/2)x ( VC8/Ls). In the first technique, the current reduction rate and the rising rate of the rectifying body D5 and D6 of the output circuit (7 3) shown in Fig. 19 are (η/?) x ( Vin/Ls) 'and Vin» VC8, resulting in a reverse recovery of the rectifier diode d5 and a corresponding negative effect. 'With the improved design of the present invention, the rectifier circuit D 5 in the output circuit (13) The rate of current drop has decreased, which means that the reverse recovery effect has been effectively suppressed. The stage of t5~t6 is as shown in the ninth figure. At t5, the reverse recovery current flowing through the rectifying diode D5 reaches a maximum value and begins to rapidly drop. The rectifying diode D 5 begins to resume blocking, its current drop rate is di/dt, and the parasitic inductance in the line A voltage spike is generated (generally small), and this voltage spike is superimposed with 2χ 1309915 (▽cs/n) to form a reverse voltage of the rectifying diode 〇5. At this time, the current flow in the ^ line is exactly the same as the stage t4~t5, except that the voltage is changed ° ° 0) - the secondary current drops rapidly from the peak, and finally reaches 丨o/n, so that the rectifying diode D5 and D6 are commutated. End. As shown in the nineteenth diagram of the prior art, the voltage spike generated by the higher voltage drop rate of the rectifier diode D5 is also higher, and the voltage spike is again 2x (Vjn/n) (non- The 2x (Vc8/n) phase is superimposed, resulting in a higher reverse voltage of the rectifier diode D5. According to the technical solution proposed by the present invention, the voltage of the rectifying diode D5 # in the output circuit (13) has been significantly reduced and improved. ~t7 stage as shown in the tenth figure. At t6, the lag bridge arm (丄2) transistor M3 achieves a zero voltage turn-off under the action of the 〇3, C4 of the lag bridge arm (1 2 ), at which time the current (iLHP) begins to charge the capacitor C3, The capacitor C4 is discharged, and the voltage across the source M3 of the transistor M3 (voltage at point c) starts to rise, and the voltage across the source and drain terminals of the transistor M4 begins to decrease. The stage of t7~t8 is as shown in the eleventh figure. At t7, the electric energy at both ends of the transistor M3 (four) rises to Vin, and the voltage across the source and drain terminals of the electric device M4 drops to 〇▽, while clamping at ον (ignoring the conduction 屙 drop of the transistor M4 body diode D4) 'The condition is established for the electric M4 zero electric shock; the energy stored in the auxiliary arm (2 0) inductor L7 starts to be fed back to the input power source, Vin through the transistor 本体4 body diode D4, flowing through the transistor μ... : The current of the mail D 4 is (i L 7 - i ρ ). 1309915 ιο from silly as shown in the twelfth figure, t8 day, the transistor Μ 4 纟 electric dust is turned on, the current flowing through the transistor Μ 4 is still (iLHp), 丨· mouth starts under the action of ^2 vjn/2 Decrease and increase in the reverse direction. When 丨[7 falls to less than..., the current flowing through the transistor M4 rises positively, and then the circuit enters the working process of the second half cycle. Since the working process of the second half cycle is similar to that of the first half cycle, it will not be detailed. The specific circuit configuration of a preferred embodiment of the present invention and its detailed working principle can be understood from the above description, and the following is summarized as follows: The transistor of the leading arm (11) _, Zero voltage switching is achieved. After the transistor is turned off, due to reflection to the transformer (10) - the secondary side load /, "lo / n' 丨〇 is the load current) participates in the parasitic capacitance to the transistors Mi, M2: 1. Charge and discharge 'this advantage for the transistors M1, M2. Electric switching, this is the base delay bridge arm of the phase-shifted full-bridge circuit (1 9 1 a & in the crystal M3, M4 ^ crystal 1" M3, M4 realize zero voltage switching 4Γ # After switching off, the secondary side of the transformer (1 0) is reflected to the -second side, 丄U; the parasitic electric I C3, C4 of the human side is not correct The transistor M3' M4 ) stores the charge stored and discharged in the leakage inductance, and simply uses the transformer (10 switching. The invention increases the force: it is difficult to make the transistor M3, realize the zero-voltage (20), the capacitance, " The bridge arm (20) uses the current supplied by the parasitic electric device of the auxiliary bridge arms M3 and M4 and the current supplied by the inductor L7 to perform the transistors C3 and C4. Discharge, it is possible to achieve 121,309,915 transistors M3, M4 zero voltage switching ..
阻斷電容C8的作用：與一般移相式全橋電路不同的 是，阻斷電容C8不僅可防止變壓器（i 〇 )偏磁，而且 在環流開始階段提供一個電壓迫使整流二極體D6導通（ 假設先前為另一整流二極體D5導通傳遞功率），從而使 變壓器二次側繞組短路，阻斷電容C8與諧振電感Ls隨即 開始諧振，使變壓器一次側電流jp由丨〇/n轉變為-丨。二 次側電流由整流二極體D5向D6轉移，當轉移完成後，整 流二極體D5實現了零電流關斷，從而抑制變壓器（1 〇 )一 _人側上整流二極體的反向恢復問題。 輔助橋臂（2 0 )白勺作用：在環流階段，變壓器（工 〇 ) 一次側電流iP在由丨0/n (或-丨0/n)轉變為_|〇/n (或 丨叫的過程中’提供一電流通路，卩防止該電流流經滯 後橋臂（12)巾電晶體M3、M4的本體二極體d3、d4 1 2 )電晶體M3、M4 電流而對電晶體M3、 滯後橋臂（1 2 )電晶 而如前揭所述，在滯後橋臂（ 切換期間，辅助橋臂（2 0 )提供 M4的寄生電容〇3、〇4充放電， 體M3、M4得以實現零電壓切換。 本發明得以其他變化設計予以 除前述第一實施例外 實現： 如第十三圖所示，其基本 ^ 土 4木稱興弟一貫施例相同，欲 強調說明的是：變壓器（1 〇 〇 ; 一入側上串接的諧振電残The function of the blocking capacitor C8: Unlike the general phase-shifting full-bridge circuit, the blocking capacitor C8 not only prevents the transformer (i 〇) from being biased, but also provides a voltage at the beginning of the circulating current to force the rectifier diode D6 to conduct ( Assuming that the other rectifying diode D5 is turned on to transmit power, so that the secondary winding of the transformer is short-circuited, the blocking capacitor C8 and the resonant inductor Ls begin to resonate, and the primary side current jp of the transformer is converted from 丨〇/n to - Hey. The secondary current is transferred from the rectifying diode D5 to D6. When the transfer is completed, the rectifying diode D5 realizes zero current shutdown, thereby suppressing the reversal of the rectifier diode on the transformer side (1 〇) Restore the problem. The role of the auxiliary bridge arm (20): In the circulation phase, the primary side current iP of the transformer (worker) is converted from 丨0/n (or -丨0/n) to _|〇/n (or squeaky During the process, a current path is provided to prevent the current from flowing through the hysteresis bridge arm (12) of the body diodes M3, M4, the body diodes d3, d4 1 2 ) the transistors M3, M4 current to the transistor M3, hysteresis The bridge arm (1 2 ) is electrically crystallized and as described above, during the lag bridge arm (the auxiliary bridge arm (20) provides the parasitic capacitance of M4 〇3, 〇4 charge and discharge, and the body M3, M4 realize zero Voltage switching. The invention has been modified in other ways to achieve the exception of the first embodiment described above: As shown in the thirteenth figure, the basic method is the same as the conventional example, and the emphasis is on the transformer (1 〇 〇; a series of resonant residuals on the input side
Ls可以是—個獨立的電感元件，亦可由變壓胃（工〇)的 13 1309915 :等效取代’原因在靖電感感值較 架構::ΙΓ圖所示，係本發明第三較佳實施例，其基本 〇)係僅由單貫犧同’不同處在於：該輔助橋臂（2 (⑴的Ϊ:=Γ7與電感L7組成，由於輔助橋臂 以確伴線路： (指電容C6、C7的電容值），可 此前提下，1 a點的電塵穩定在Vin/2’且紋波較小；在 辅助橋臂（2 〇 )可以採用i_c來代替 採用LC線路日4LCC ? 裏路日”在早-電容C7的狀況下’其電容值取大 、° —保a點電壓穩定在Vin/2，且紋波較小。 架構係本發明第四較佳實施例’其基本 …、…"目同，不同處在於1輔助橋臂（2 =加了 _電感L8，該電感以係串接於兩電容 連接節點a與阻斷電容C8(b點）之間。由於全 在二載或輕载情況下，電流丨〇/n較小 Γ4仃=:，可能使電晶體M1、M2的零電遷切換較 =現*在輔助橋臂（20)中加入另一電感L8，即可 “、-路輔助電流對電晶體M1、M2的寄生電容ci、c2 厂 =放電’使㈣現零電 變二各=:針:㈣ 除此以外，本發明亦可針對變壓器（i 〇 ) _ 次側之輪出電路（1 3 )作變化設計： - 】4 1309915 〇如第十六圖所示，係本發明第五較佳實施例，其基本 架構仍與第一實施例相同’不同處在於：該輸出電路（工 3 )中作為全波整流的整流二極體D5、D6可由一橋式整 流器D5〜D8所取代。 。如第十七圖戶斤#，係本發明第六較佳實施例，其基本 架構與第一實施例相同，不同處在於：該輪出電路（" )中的輸出電感L5由輸出端正端調換至負端。 如第十八圖所示，係本發明第七較佳 ，與第-實施例相同…處在於:該輸出丨電路= 3)中的整流二…5、〇6極性互換，此係由於變壓哭 1 〇)二次側的繞組對稱，故將整流二極體D5' D6極 ί·生互換，不致影響電路的正常工作。 【圖式簡單說明】 第—圖：係本發明第—較佳實施例的詳細電路圖。 。第二圖：係本發明第—較佳實施例的工作週期時序圖 心二三〜十二圖：係本發明第-較佳實施例標示有工作 週期中電流流動方向符號的詳細電路圖。 有工作 第十三圖：係本發明铰_ 第一 k佳實施例的詳細電路 第十四圖：係本發明第电略圖。 弟—較佳實施例的詳細 第十五圖：係本發明筮电峪圖。 月第四較佳實施例的詳細 第十六圖：係本發明箪π & 电路圖。Ls can be a separate inductive component, or can be replaced by a pressure-changing stomach (Working Industry) 13 1309915: Equivalent to the reason why the inductor inductance value is compared with the architecture:: the figure shows the third preferred embodiment of the present invention. For example, the basic flaw is only a single sacrifice. The difference is: the auxiliary bridge arm (2 ((1) Ϊ:=Γ7 and inductor L7, because the auxiliary bridge arm is indeed accompanied by the line: (refers to the capacitor C6, C7 capacitance value), under this premise, the electric dust at 1 a point is stable at Vin/2' and the ripple is small; in the auxiliary bridge arm (2 〇), i_c can be used instead of LC line day 4LCC? In the case of the early-capacitor C7, the capacitance value is large, and the voltage at the point a is stabilized at Vin/2, and the ripple is small. The architecture is the fourth preferred embodiment of the present invention. ... " the same, the difference lies in 1 auxiliary bridge arm (2 = added _ inductor L8, the inductance is connected in series between the two capacitor connection node a and the blocking capacitor C8 (point b). Because all in two Under load or light load, the current 丨〇/n is smaller Γ4仃=:, which may cause the zero-electron switching of the transistors M1 and M2 to be compared with the current* in the auxiliary bridge arm (20). An inductance L8, that is, ", - the auxiliary current to the parasitic capacitance of the transistors M1, M2 ci, c2 factory = discharge ' (4) the current zero electricity = two:: needle: (4) In addition, the present invention can also be directed to Transformer (i 〇) _ secondary side wheel-out circuit (1 3 ) for change design: - 4 4 1309915 As shown in the sixteenth figure, the fifth preferred embodiment of the present invention, the basic architecture is still the first The same is true in the embodiment. The difference is that the rectifier diodes D5 and D6, which are full-wave rectified in the output circuit (work 3), can be replaced by a bridge rectifier D5 to D8. According to a sixth preferred embodiment of the present invention, the basic architecture is the same as that of the first embodiment, except that the output inductor L5 in the round-trip circuit (") is switched from the positive end of the output terminal to the negative terminal. The seventh preferred embodiment of the present invention is the same as the first embodiment. The output is 丨 circuit = 3) the rectification of the second ... 5, 〇 6 polarity interchange, this is due to the pressure change crying 1 〇) twice The windings on the side are symmetrical, so the rectifying diode D5' D6 is interchanged and does not affect the normal operation of the circuit. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a detailed circuit diagram of a preferred embodiment of the present invention. FIG. 2 is a timing diagram of a duty cycle of the first preferred embodiment of the present invention. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT A detailed circuit diagram showing the direction of current flow direction in a duty cycle. Operational Fig. 13: The hinge of the present invention - Detailed circuit of the first preferred embodiment Fourteenth embodiment: BRIEF DESCRIPTION OF THE DRAWINGS The fifteenth drawing of the preferred embodiment is a circuit diagram of the present invention. A detailed sixteenth embodiment of the fourth preferred embodiment of the present invention is a circuit diagram of the 箪π &
^ 第五車又佳實施例的詳細電路R 第十七圖··係本發明宽丄 圖。 弟/、私佳實施例的詳細電路 15 1309915 第十八圖：係本發明第七較佳實施例的詳細電路圖。 第十九圖：係一種已知移相式全橋電路的詳細電路圖 第二十圖：係又一種已知移相式全橋電路的詳細電路 圖。 第廿一圖：係再一種已知移相式全橋電路的詳細電路 圖。^ The detailed circuit of the fifth embodiment of the preferred embodiment of the fifth embodiment is a wide view of the present invention. Detailed circuit of the parent/private embodiment 15 1309915 FIG. 18 is a detailed circuit diagram of a seventh preferred embodiment of the present invention. Fig. 19 is a detailed circuit diagram of a known phase-shifted full-bridge circuit. Fig. 20 is a detailed circuit diagram of a known phase-shifted full-bridge circuit. Figure 1: A detailed circuit diagram of a known phase-shifted full-bridge circuit.
(1 1 )超前橋臂 (1 3 )輸出電路 (71)超前橋臂 (7 3 )輸出電路 【主要元件符號說明】 (1〇)變壓器 (1 2 )滯後橋臂 (2 0 )輔助橋臂 (7 0 )變壓器 (7 2 )滯後橋臂(1 1) Leading bridge arm (1 3 ) Output circuit (71) Leading bridge arm (7 3 ) Output circuit [Main component symbol description] (1〇) Transformer (1 2 ) Hysteresis bridge arm (2 0 ) Auxiliary bridge arm (7 0 ) transformer (7 2 ) lag bridge arm
1616