TWI295792B - - Google Patents

Description

1295792 IX. Description of the invention: [Technical field to which the invention belongs]

The present invention relates to a self-luminous display panel such as an EI^M non-panel using an organic or inorganic electroluminescence (EL) element, and a driving circuit (ic) relating to such display panels and the like, and a driving method relating to an EL display panel or the like And the use of such information display devices and the like. [Prior Art] As for the σ, the active matrix type display device arranges a plurality of pixels in a matrix to control the light intensity of the pixels in accordance with the given image signal so as to display an image. For example, liquid crystal is used as the electrical optical object (4), the pixel transmittance is known, and the voltage of each pixel is changed. ^ Organic electroluminescence is used (= active matrix type of material material optical optical converter f) The luminance of the image display device changes in accordance with the current written to the pixel.

Each pixel of the attack panel is operated as a shutter, and the light from the f light is turned on and off by using the pixel of 4 as the shutter, and the display image is read. The organic EL display panel has self-luminous light of each pixel. Type, I ancient car 乂; liquid day and day display panel, organic EL display panel has the advantages of image recognition, no backlight, fast response. The brightness of each of the light-emitting elements (pixels) of the organic display panel is different from that of the liquid crystal display panel by the current ^::, which is the light-emitting current-driven type or the current-controlled type. The _^ display panel can also be constructed by a simple matrix method and an active matrix method. It is simple and easy to achieve high-definition but low-cost; the latter can realize large-scale, high-definition display panels, 94992-961016.doc 1295792 However, there are problems in that the control method is technically difficult and expensive. Nowadays, the development of the active matrix method is frequently performed. The active matrix method is controlled by the thin film transistor (transistor) disposed inside the pixel, and is controlled to flow in each pixel. The current of the light-emitting element. The pixel 16 of the active matrix type organic EL display panel is composed of the EL element 15 of the light-emitting element, the first transistor 11a, the second transistor Ub, and the storage capacitor 19. The light-emitting element 15 is organic In the present invention, the transistor na for supplying (controlling) a current to the EL element 15 is referred to as a driving transistor 11. In many cases, the organic EL element 15 is called an OLED because of its rectibility. The organic light-emitting diode is a diode mark as the light-emitting element (4) in Fig. 1#. However, the light-emitting element 15 of the present invention is not limited to the germanium LED. It can be controlled by the motor flowing into the component 15. For example, an inorganic component is exemplified, and a white light-emitting diode composed of a semiconductor is exemplified, and a general-purpose light-emitting diode is exemplified. The transistor may also be required. Further, the hair 7L member 15 is not necessarily required to have rectifying property, and may be a bidirectional diode. The EL element 15 of the present invention may be used for any of the reasons. The problem of the life of the component, the current, and the current. Because the display of the private organic EL element is used for the illumination of the current organic EL element, the written eve of the song is proportional to the current flowing into the device. Therefore, in the case where the amount of illuminating is large, the θ pixel has a large current flowing into the device to cause deterioration of the element, or it is necessary to have a large-capacity power supply for the maximum current amount. 94992- 961016.doc 1295792 [Summary of the Invention] Since the amount of luminescence of the display system for the organic EL element is proportional to the amount of current flowing into the device, the maximum luminescence of the component is improved. In the case of the 发光 胄 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 在 电流 电流 电流 电流 电流 电流 电流 电流 电流 电流 电流 电流 电流 电流 电流 电流 电流The driving method of the self-luminous display device of the present invention is a method in which a plurality of self-luminous elements constituting each pixel are arranged in a matrix in the pixel row direction and the pixel column direction, and current flows into the respective I. Between the anode electrode and the cathode electrode of the light-emitting element, so that each of the pixels emits light for driving the display portion; and the method includes: a first process of performing image data corresponding to the input from the outside, obtaining: flowing into the anode electrode and a first current amount between the cathode electrodes, wherein the first current amount is not limited to a distribution of image data values around the image data, and a predetermined single value is obtained; and the second processing corresponds to The image data input from the outside is set to set a second current ΐ ' between the anode electrode and the cathode electrode, and the second current amount is According to the foregoing image of the periphery of the image data, the distribution of the data values, preparing a processor that suppresses the value of the first current amount by a specific ratio and the suppression ratio may be changed according to the distribution of the image data values; and according to the foregoing Or as a result of the second processing means, controlling the amount of current flowing into each of the pixel columns to cause the display portion to emit light. For example, the driving method of the self-luminous display device of the present invention, wherein the gray value of the image data from the external input is located at a ratio of the first:: 疋 gray value is for the purpose of performing the method of driving the self-luminous display device of the present invention. When the black side is displayed on the low gradation side, the first current amount applied between the anode and the cathode electrode of the corresponding respective light-emitting elements is determined by the above-described first processing. The driving method of the self-luminous display device according to the invention, wherein the third embodiment of the invention is that the gray value of the image data from the external input is located at a higher gray level for the white display than the first temple fixed fire value. In the case of the side, the second current amount X applied between the anode electrode and the cathode electrode corresponding to the respective light-emitting elements is determined by the above-described two processes. When the first current amount is 乂, the following relationship is established between the current amount y and the second current amount X: 〇.20y$ 〇·6〇” as the first 1st third A driving method of the self-luminous display device of the present invention, wherein the fourth present invention is the current value il obtained by the maximum value of the image data input from the outside by the first application of the current amount The image data of the input during the second period is calculated by calculating an appropriate electric scratch value 12' according to the ratio l2/il, and sequentially calculating the foregoing for each of the specific image data input according to the second and the second input. Pixel The method of driving a display device according to any one of the first to third aspects, wherein: the fifth invention is the second method of applying the current amount by obtaining a maximum value of the image Ί maximum value of the input image The current value l3' is actually applied between the anode electrode and the cathode electrode of the respective light-emitting elements, and the optimum current value of the current value i49' is calculated by multiplying the ratio i4/i3 by the optimum current 9492-961016.doc 1295792 The image (4) = 贞 ' 以便 以便 以便 以便 以便 以便 以便 以便 以便 ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' ' Driving the production letter ^: The invention is based on the external input of the aforementioned image data gray-/di"-specific gray value is located on the high gray side for white display, ^ black = rate control applied to the aforementioned respective light-emitting elements The method of driving the self-luminous display device according to the eighth aspect of the present invention, wherein the seventh invention is performed by the first column to the terminal column. , In the seventh embodiment of the present invention, the black insertion is performed by the first column to the terminal column in the foregoing U贞. The method for driving the self-luminous display device according to the sixth aspect of the present invention, wherein the ninth invention is that the black insertion is not divided into a plurality of regions and inserted into a plurality of regions. The method of the self-luminous display device of the present invention according to any one of the first to third aspects, wherein the tenth invention is the external image input from the outside. The gray value of the data is located on the high gray side of the white display for the first specific gray value, and the current amount between the anode electrode and the cathode electrode of the respective light emitting elements is adjusted to adjust the inflow source line. The amount of current in the group is controlled. The driving method of the self-luminous display device according to the tenth invention, wherein the invention flows into the foregoing complaint; the first current amount of the first pole group is 1, 13 The aforementioned adjustment is performed by increasing or decreasing the reference current value. According to a tenth aspect of the present invention, in the driving method of the self-luminous display device, the second adjustment of the current amount of the source line group of the present invention is performed by increasing or decreasing the number of gradations. The driving method of the self-luminous display device of the present invention, wherein the thirteenth invention is obtained between the anode electrode and the cathode electrode of the respective I-lighting 7L member between the first and the third The first electric "the difference between the second motor flowing in during the second frame period between the second and the second" is calculated by the difference between the first motor and the second differential current value η (n is a differential current value γ of 1 or more by the foregoing The η differential current value determines the selected value of the pixel column. The driving method of the self-luminous display device of the eleventh embodiment, wherein the fourteenth invention is such that the η value is 4 g η ^ 2 $ 6. The driving method of the self-luminous display device of the present invention, wherein the fifteenth invention is corrected by the amount of current flowing between the anode electrode and the cathode electrode of the respective light-emitting elements. The fifteenth invention is a driving method of the self-luminous display device, wherein the tenth/the present invention is that the r constant is a set of points on a curve formed by sequentially combining the intermediate values of the complex seven curves. Fifteenth hair The driving method of the self-luminous display device according to the seventh aspect of the present invention, wherein the increase or decrease of the 7 constant is adjusted by the length of the light emitting period of the self-luminous element. The self-luminous display device of the present invention Driving method 94092-961016.doc 1295792 Method/Twenty-eighth invention is configured to control the cutting means of the second processing means to control the cutting of the second processing, so as to facilitate the entry, the aforementioned first processing and the foregoing a combination of the second process for determining a current amount between the anode electrode and the cathode electrode of each of the light-emitting elements of the current source, wherein: the anode electrode flowing into the respective light-emitting elements is determined by the first process and the foregoing The amount of current between the cathode electrodes. The driving circuit of the self-luminous display device of the present invention is characterized in that a plurality of self-luminous elements constituting each pixel are arranged in a matrix in a pixel row direction and a pixel direction; Between the anode electrode and the cathode electrode of each of the aforementioned light-emitting elements, so that the respective pixels emit light for display; Having: " another eight...β π 曰 邵 邵 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入 输入The distribution of the brightness of the pixel's brightness is determined by the second brightness adjusted by the above-mentioned first-brightness method set in advance from the image data of the external input. The invention relates to a driving electric device of a self-luminous display device, which is configured such that a plurality of self-luminous elements constituting each pixel are arranged in a matrix in a pixel row direction and a pixel misalignment direction, and current flows to the respective respective light-emitting elements of the present invention. And a cathode display portion for causing each of the pixels to emit light, and a positive display portion; wherein: the material first processing means is configured to correspond to an image input from the outside, and is set to flow between the anode electrode and the cathode electrode First Bayer 94992-961016.doc -11 - 1295792 flow, and the aforementioned first-current amount is not limited to the distribution of image nurturing values around the aforementioned image data, Setting a predetermined single-value processor; / - a second processing means for setting a second current amount between the anode electrode and the cathode electrode corresponding to the image poor material input from external input The second current amount is based on the front of the image (4) before: the shadow, the data value distribution condition 'preparation' is fixed at a specific ratio to suppress the value of the first current amount, and the suppression ratio can be changed according to the condition of the image data value. And a control means for controlling the amount of current flowing into each of the pixel columns based on the results of the first and second processing means. For example, the driving circuit of the self-luminous display device of the twentieth invention, the twentieth-the present invention is the second processing circuit, according to the image data input from the outside, by the arithmetic processing, The processing of the aforementioned first current amount in each pixel column is determined. The driving circuit of the self-luminous display device according to the tenth aspect of the present invention, wherein the arithmetic processing of the twenty-second invention obtains a current value η of a maximum value of the image data input from the portion during the _th period, Calculating an appropriate current value 丨/ by the operation of the image data input during the second period, and sequentially calculating, according to the proportional coffee, the aforementioned pixels applied to the specific image data input according to the second period input The processing of the amount of current. According to a driving circuit of the self-luminous display device of the twentieth invention, in the twenty-third aspect of the invention, the second processing circuit has means for measuring the image data input from the outside, and determining, according to the measurement result, 94992-961016.doc -12- 1295792 The arithmetic processing of the aforementioned second current amount of the pixel column. Such as the first - the first one. One Ding two of the invention's self-hairpin display + following the m " especially, the driver does not set the drive circuit, the second = the calculation of the material before the invention is obtained =: the largest data The third current value of the value is actually applied to the current optimum value between the anode electrode and the cathode electrode, and the value is taken as the first: current value M, and the ratio 1 is 1;; (4), (4) Processing of the above-mentioned image, sequence 4 applied to the amount of current of the material before the display. Nineteenth to fourteenth, the self-luminous display device of the present invention: drive: road 'the twenty-fifth The invention includes a switching means for the second processing means to operate only by the first means: the controller of the self-luminous display device of the present invention, which is the nineteenth to the twenty-fourthth The driving circuit of the present invention, wherein the self-luminous display device of the present invention has the driving circuit of the invention of the nineteenth aspect, and the self-luminous element h and the pixel The financial direction is arranged in a matrix. The self-luminous display device of the present invention is a driving method for a self-luminous display device, which is configured by a plurality of self-luminous 7L elements constituting each pixel arranged in a matrix in a pixel row direction and a pixel column direction, and a current is applied. Flowing between the anode electrode and the cathode electrode of the respective light-emitting elements to cause the respective pixels to emit light for driving the display portion; and controlling the amount of current flowing in each of the pixel columns according to the result of the first or the third processing means, The first processing is performed to obtain a first current amount between the electrode of the anode 94992-961016.doc -13 - 1295792 and the cathode electrode corresponding to the image data input from the outside. And the first current amount is not obtained according to the distribution of the image data values surrounding the image data, and the processor is configured to obtain a predetermined single value; and the second processing is performed by the corresponding image data corresponding to the external input. a second amount of current flowing between the anode electrode and the cathode electrode, and the second current amount is according to the image data The side of the image data value distribution state is prepared by a processor that suppresses the value of the first current amount by a specific ratio, and the suppression ratio is variable according to the distribution of the image data values; and is equivalent to performing white display. The current amount is expressed as 1 〇〇. For the gradation of the low current region in which the specific current amount is expressed by 30 or less, a positive number of N1 > 丨, N2 > 0 and N1.N2 is set. For the coefficient, set the aforementioned specific current amount to w, and set the current value at this time to

When Iorg ' is set to T 〇 rg, the amount of current that satisfies the electric power 11 value Ι〇Γ§ χΝ 1 and the illuminating period is Torgxl / N2 is applied instead of the aforementioned current amount. [Embodiment] In the present specification, in order to facilitate understanding of each drawing or/and easy drawing, there is a need to omit or/and zoom in and out. For example, in the cross-sectional view of the display panel illustrated in Fig. u, the sealing film lu or the like is sufficiently thickened and shown. On the other hand, the sealing cover 85 is thinned as shown in Fig. 10'. Also, there are some omissions. For example, the display panel or the like of the invention is omitted in order to prevent phase C such as unnecessary light reflection. The above matters are also the same for the following figures. Also, " squatting or squatting has the same or similar type, material, function or action. Furthermore, the contents described in the drawings and the like may be combined with other embodiments such as 94992-961016.doc • 14-1295792, even if it is not specifically stated. For example, a touch panel or the like can be attached to the display panel of Fig. 8 as the information display device shown in Figs. 34 and 52 to Μ. Further, a magnifying glass 342 may be attached to constitute a viewfinder (refer to Fig. 34) for use in a camera (refer to Fig. 52, etc.). Further, the driving method of the present invention as described in Fig. 4, Fig. 15, Fig. 18, Fig. 21, Fig. 21, and the like can be applied to any of the display devices or display panels of the present invention. In summary, the driving method described in the present specification can be applied to the display panel of the present invention. Further, the present invention is mainly applied to an active matrix display panel in which a transistor is formed in each pixel. However, the present invention is not limited thereto, and it is also applicable to a simple matrix type. In this case, the items, contents, and styles described or illustrated in the drawings and drawings may be combined with each other and described in the request, and it is not possible to describe all the combinations in the specification or the like. In recent years, an organic EL display panel in which a plurality of organic electroluminescence (EL) elements are arranged in a matrix has been attracting attention as a display panel which is low in power consumption and high in display quality and which can be made thinner. As shown in FIG. 10, the organic EL display panel is formed on a glass plate 71 (array substrate) on which a transparent electrode 105 as a pixel electrode is formed, and at least one layer composed of an electron transport layer, a light-emitting layer, a hole transport layer, and the like is laminated. The organic functional layer (EL layer) 15 and the metal electrode (reflective film) (cathode) 1〇6. A positive voltage is applied to the anode (Anode) of the transparent electrode (pixel electrode) 1 〇 5, and a negative voltage is applied to the cathode of the metal electrode (reflecting electrode) 106, that is, by applying a direct current to the transparent electrode 1 Between the 〇5 and the metal electrode 106, the organic functional layer (EL layer) 15 emits light. By using an organic compound which can expect good luminescence characteristics for an organic functional layer, the EL display panel can be practically used in the manner of 94992-961016.doc -15-1295792. Further, the present invention is described by taking an organic EL display panel as an example. However, the present invention is not limited thereto, and can be applied to a display using an inorganic EL or a display using a self-luminous element such as FED or SED. Further, the structure, the circuit, and the like are also applicable to other display panels such as a TN liquid crystal display panel and an STN liquid crystal display panel. Hereinafter, the manufacturing method and structure of the EL display panel of the present invention will be described in detail. First, a transistor u for driving a pixel is formed on the array substrate 71, and one pixel is composed of two or more, more preferably four or five transistors. Further, the pixel current is programmed, and the programmed current is supplied to the EL element 15. Typically, the current programmed value is held as a voltage value by the storage capacitor 19. The pixel configuration of the combination of the electrodes 11 and the like will be described later. Next, a pixel electrode as a hole injecting electrode is formed in the transistor 11, and the pixel electrode 1〇5 is patterned by photolithography. Further, a light-shielding film is formed or disposed on the lower layer or the upper layer of the transistor u to prevent deterioration of the enamel caused by the photoconductance of the light incident on the transistor. Further, the so-called current program is applied from the source driver circuit 丨4 to the pixel (or from the pixel to the source driver circuit _M) so that the pixel maintains a signal value corresponding to the current. A current corresponding to the value of the apostrophe held therein flows into the EL element 15 (or the *EL element 15 flows in). In summary, the current is stylized, and a current equivalent to (corresponds to) the stylized current flows into the EL element 15. Another aspect is a voltage program in which a source driver circuit 14 applies a 耘 voltage to a pixel to maintain a pixel value corresponding to the voltage. A current flow corresponding to the voltage held thereby, the EL element 15. In summary, 94992-961016.doc -16 - !295792 is programmed with voltage to convert the voltage into a current value in the pixel, and a current equivalent to (corresponding to) the stylized voltage flows into the EL element 15. The active matrix method used in the organic EL display panel must meet the following two conditions. K selects (four) pixels to give the necessary display information. 2. Current can flow into the EL element during one frame period. In order to satisfy these two conditions, the conventional organic EL pixel structure-the transistor m shown in FIG. 76 is used as a switching transistor for selecting a pixel, and the second transistor 1 la is used to supply a current to the EL. The element (the transistor for driving the el film opening 5) Λ In this case, if the liquid crystal is used in comparison with the active matrix method for liquid crystal, the switching transistor m' is required for the liquid crystal, but in order to turn on the device 15, it is necessary to drive the electric power. Crystal 11 a. The reason is that the liquid crystal eve 4 Bu main # you, Xin Rizhi can be kept open by applying a voltage, but the EL element 15 is in the case of green *, h, where right Continuously flowing current will not be able to maintain the lighting state of the pixel 16. Therefore, in order to continue the current flow in the EL display panel, the transistor 11a must be continuously turned on. First, if it is scanned against the green part. When both the trace line and the data line are turned on, the electricity is stored in the Leijiao Gandian Valley state via the switch transistor 11b. The capacitor i9 continuously applies a voltage to the gate of the drive transistor 11a. Therefore, even if the switching transistor m is turned off, the current is still Continued to flow in from the current supply line, the pixel 16 can be turned on during one frame period. The voltage according to the gradation must be applied to the extreme voltage. Therefore, when the driving transistor 11a is used to display the gradation, the driving power is used. The change of the on-current of the gate of the crystal 11a will be directly expressed in the display. If the transistor crystal is formed by a single crystal, the on-current of the transistor is extremely uniform, but it can be formed on an inexpensive glass substrate to form a temperature. The low temperature polycrystalline transistor formed by the low temperature polysilicon technology of 450 degrees or less has a variation in the threshold value within a range of ±0.2 V to 0.5 V. Therefore, the opening current flowing through the driving transistor 11a This varies depending on this, and display unevenness occurs. These unevenness occur not only in the fluctuation of the threshold voltage but also in the mobility of the transistor, the thickness of the gate insulating film, etc. Deterioration, characteristics also change. Furthermore, it is not limited to low-temperature polysilicon technology, and can also be constructed by high-temperature polysilicon technology with a process temperature of 45 ( (Celsius) or higher. A semiconductor film deposited by a solid phase (CGS) forms a TFT, etc. Further, an organic TFT 〇 can be used, and a TFT array formed by an amorphous germanium technique can be used to form a panel. Further, the present specification mainly describes a TFT formed by low-temperature polysilicon, but The problem of the occurrence of the change of πτ is the same in other ways. Therefore, in the analogy method of displaying the gradation, in order to obtain the display of the uniform sentence, the characteristics of the device must be strictly controlled, and the current low-temperature polycrystalline crystal can not be: In order to solve this problem, the method of "suggesting the variation of the threshold voltage by a capacitor to obtain a uniform hook current" is considered by thinking of setting up four or more transistors in one pixel. Or a method of forming a steady current circuit every \ pixels to achieve current uniformity. However, these methods are due to the stylized current passing through the anal element 15 = therefore when the current path changes 'for the switch connected to the power line: the transistor of the moving current becomes the source with the fuse, the driving margin becomes 乍, so There is a problem that the driving voltage becomes high. 94992-961016.doc -18 - 1295792 Further, it is necessary to use a switching transistor connected to a power supply in a region where impedance is low, and this operation range is affected by variations in characteristics of the EL element 15. In addition, the voltage-current characteristics in the saturation region have a problem of fluctuations in the current value of the memory when the kink ML occurs or the threshold voltage of the transistor fluctuates. In view of the above problems, the EL element structure of the present invention controls the transistor of the current flowing into the EL element 15 not to become a source follower, and even if the transistor has a kink current, the influence of the kink current can be suppressed. The smallest, reducing the composition of the change in the current value of the memory. Specifically, as shown in FIG. 1 , the pixel structure of the EL display device of the present invention is formed by overlapping a plurality of transistor electrodes and EL elements composed of at least four unit pixels, and further forming a pixel electrode and a source signal line. . In summary, on the source #线线线8, a flattening film composed of an insulating film or an acrylic material is formed and insulated, and the insulating film is formed as a pixel electrode 1〇5. The configuration in which the pixel electrodes are superimposed on the source signal line 18 is referred to as a high aperture ratio (HA) configuration. By driving the gate signal line (first scanning line) 17a (applying an on voltage), the transistor (transistor or switching element) Ua and the electrode (transistor or switching element) for driving via the ELtc device 15 are driven. i丨c, the current value flowing into the EL element 15 from the source driver circuit 丨4. Further, in order to short-circuit the gate and the drain of the transistor Ua, the transistor 11b is turned on by the gate signal line 17a (applying an on-voltage), and is connected to the idler and the drain of the transistor Ua. Capacitor (capacitor, storage capacitor, additional capacitor) 19, the gate voltage (or drain voltage) of the memory transistor 11a, so that the aforementioned current value flows into the 94092-96l0l6.doc -19-1295792 ( Refer to Figure 3(a)). Further, the capacitance (capacitor) 19 between the source (s) and the gate (G) of the transistor 11a is preferably a capacitance of Ο·2 pF or more. The configuration of forming the capacitor 19 is also exemplified as another configuration. In summary, the capacitor electrode layer, the gate insulating film, and the gate metal form a storage capacitor. From the viewpoint of preventing the decrease in the degree of turbulence caused by the leakage of the transistor llc, and in order to stabilize the display operation, it is preferable to form the capacitor as such. Further, the size of the capacitor (storage capacitor) i 9 is preferably 〇·2 PF or more and 2 PF or less, and the size of the capacitor (storage capacitor) 19 is preferably 0.4 pF or more and ι·2 pF or less. Further, the capacitor 19 is preferably formed substantially in a non-display area between adjacent pixels. Generally, when the color organic E] L15 is formed, since the organic EL layer 15 is formed by vapor deposition using a mask of a metal mask, The positional deviation of the mask occurs, and the positional deviation of the formation of the EL layer occurs. If a positional deviation occurs, it is feared that the organic EL layers 15 (15R, 15G, 15B) of the respective colors overlap. Therefore, the non-display area between adjacent pixels of each color must leave! 〇 μ m or more. This part will become a part that does not help to shine. Therefore, the formation of the storage capacitor 19 in this region is an effective means for increasing the aperture ratio. Further, the metal mask is made of a magnet, and the metal mask is magnetically attracted by the magnetic force from the back surface of the substrate 71. The metal mask is seamlessly bonded to the substrate by magnetic force. The matters relating to the above manufacturing methods are also applicable to other manufacturing methods of the present invention. ... secondly, the gate signal line 17a is deactivated (applying a turn-off voltage), and the gate 7 5 tiger line 17b is actuated to switch the flow path of the current to include the electricity connected to the first transistor 11a and the EL element 15. The crystal nd, and the path of the aforementioned anal element 94092-96l016.doc -20-1295792 15, causes the memory current to flow into the aforementioned el element i5 (see Fig. 3(b)). " This circuit has four transistors 11 in one pixel, and the gate of the transistor Ua is connected to the source of the electric a body 11b. Further, the transistor 11b and the gate of the transistor are connected to the gate signal line 17a. The drain of 1 lb of the transistor is connected to the source of the transistor 11c and the source of the transistor Ud, and the drain of the transistor iic is connected to the source k line 18. The gate of the transistor 11d is connected to the gate signal line, and the drain of the transistor lid is connected to the anode electrode of the EL element 15. Furthermore, in Figure 1, all of the transistors are constructed of p-channels. The mobility of the p-channel is somewhat lower than that of the N-channel electro-thoracic body, but it is suitable because it has a large withstand voltage or is less prone to deterioration. However, the present invention is not limited to the configuration of the P-channel, but may be constituted by only the N-channel, and may be composed of both the N-channel and the p-channel. Further, in Fig. 1, the transistors 11c and lib are formed of the same polarity and are formed of N channels, and the transistors φ and nd are preferably constituted by p channels. In general, a p-channel transistor has a high reliability and a kink-electrode characteristic compared to an N-channel transistor. For an EL element 15 that controls the current to obtain a desired luminous intensity, the transistor 11a is a p-channel. The effect is greater. It is most suitable to form all of the TFTs 11 constituting the pixels by the p-channel, and the built-in gate driver 12 is also preferably formed by the P-channel. By forming the array in only the p-channel, the number of masks is five, and the cost can be reduced and the yield can be improved. Hereinafter, in order to further facilitate the understanding of the present invention, the EL element configuration of the present invention will be described with reference to FIG. The el element configuration of the present invention is controlled by two timings. The first timing is the timing of the necessary current value for memory. At this timing, by using the 94921-961016.doc -21 - 1295792, the electric celestial body llb and the transistor Ue are turned on as the equivalent circuit, and the figure () is here. The specific current Iw is written by the signal line. Thereby, the transistor. When the gate is connected to the gate, current flows in through the transistor 11a and the transistor 11c. Therefore, the voltage of the gate source of the transistor lu is the voltage V1 flowing into the voltage 11. The first timing is the timing at which the transistor Ua and the transistor llc are turned off, and the transistor 11d is turned on. At that time, the equivalent circuit becomes Fig. 3(b), and the voltage between the source gates of the transistor 11a is maintained as it is. In this case, since the transistors 11 & often operate in a saturated region, the current of Iw is constant. The right action is as shown in Figure 5. In summary, 5i a of Fig. 50) indicates a pixel (column) (written pixel column) that is subjected to current programming at a certain time on the display screen 50. As shown in FIG. 5(b), the pixel (column) 5U is a non-lighting (non-display pixel (column)), and the other pixels (columns) are display pixels (columns) 53 (current flows into the EL element 15 of the non-pixel 53). , EL element 15 emits light). As shown in Fig. 3(a), in the case of the pixel configuration of the figure, in the current program, the program current Iw flows into the source signal line 18, and the current flows through the transistor na, and the capacitor 19 performs voltage setting (program). In order to keep the current flowing into lw. At this time, the transistor 1 id is in an on state (off state). When the current flows into the el element 15 as shown in Fig. 3(b), the electromorph 11c is turned off, and the transistor 11d operates. In summary, the off voltage (Vgh) is applied to the gate signal line 17a, and the transistors 11b, Uc are turned off. On the other hand, the turn-on voltage (Vgi) is applied to the gate signal line 17b, and the transistor 11d is turned on. This timing chart is shown in Figure 4. Furthermore, in Fig. 4 and the like, the characters in the brackets (for example, 94992-961016.doc -22-1295792, such as '(1), etc.) indicate the number of the pixel columns. In summary, the gate signal line HaQ) represents the gate signal line 17a of the pixel column (1), and * H of the upper portion of Fig. 4 indicates the horizontal scanning period. In summary, 1H is the first horizontal scanning period. Furthermore, the above matters are not limited as long as they are easy to explain (number 1H, 1H cycle, order of pixel column numbers, etc.). As can be seen from Fig. 4, in each of the selected pixel columns (ih in the selection period), when the turning-on voltage is applied to the gate signal line 17a, the turn-off voltage is applied to the gate signal line 17b. Also, during this period, the current does not flow through the element 15 (non-lighting state). In the unselected pixel column, the turn-off voltage is applied to the gate signal line 17a, and the turn-on voltage is applied to the gate signal line 17b, and during this period, current flows into the EL element 15 (lighting state). Furthermore, the gate of the crystal 11 b and the gate of the transistor 11 c are connected to the same gate signal line 17a, but the gate of the transistor Ub and the gate of the transistor Uc may be connected to different gate signal lines. 17. The gate signal line of 1 pixel is 3 (the structure of Figure 1 is 2). By individually controlling the on/off timing of the gate of the transistor Ub and the on/off timing of the gate of the transistor i lc , the variation of the current value of the 2EL element 15 caused by the variation of the transistor 11a can be further reduced. By combining the gate #1 line 17a and the gate signal line 17b to form a different conductivity type (N channel and p channel) of the transistor 11c and the lid, the simplification of the driving circuit can be achieved, and the aperture ratio of the pixel can be improved. The configuration is as described above, and as the operation timing of the present invention, the write path from the signal line is turned off. That is, when a specific current is memorized, if the flow path of the current has a branch, the correct current value is not stored in the source (s)_the idle (G) capacitor (capacitor) of the transistor 11a. By making the transistor ilc and the transistor lld 94992-961016.doc 23 1295792 different conductivity types, the timing of the switching, lid. 'In order to control the threshold of each other, the transistor can be turned on after the transistor 1 lc is turned off in the scanning line. The purpose of the invention is to propose that a change in the characteristics of the transistor does not affect the circuit configuration of the display, and therefore requires 4 above the transistor. When the circuit constant is determined based on the characteristics of the electric crystals, if the characteristics of the four transistors do not match, it is difficult to obtain an appropriate circuit constant. For the long-axis direction of the laser irradiation, the channel direction is horizontal and vertical, and the threshold and mobility of the transistor characteristics are different. Moreover, the degree of change in any case is the same. In the horizontal direction and the vertical direction, the average values of the mobility and the threshold value are different. Therefore, the channel directions of all the transistors constituting the pixel should be the same. In Fig. 27, when the current flowing into the EL element 15 is set, the signal current flowing into the transistor 271a is Iw, and as a result, the voltage between the gate and the source generated in the transistor 271a is Vgs. At the time of writing, the transistor ?101 is short-circuited between the gate and the drain of the transistor 271a, so that the transistor 2 71a operates in the saturation region, so Iw is given by the following equation. (Formula 1)

Iw = μ1 · Coxl · { Wl / (2 · L1)} · (Vgs - Vthl) 2 where ' Cox is the gate capacitance per soap area, given by C 〇 x = g 〇 · 8r / d. Vth represents the threshold of the transistor, μ represents the mobility of the carrier, w represents the channel width, L represents the channel length, ε Ο represents the vacuum mobility, ε Γ represents the relative dielectric constant of the gate insulating film, and d is the gate insulating film The thickness. If the current flowing into the EL element 15 is Idd, the Bayer Odd is controlled by a voltage region electro-optical crystal 27b between 94992-961016.doc -24·1295792 connected in series to the EL element 15. In the present invention, the gate_source is coincident with the Vgs of (Formula 1), so if the transistor 丨b is assumed to be saturated, the following equation will hold. (Formula 2)

Idrv = μ2 · Cox2 · { W2/(2 · L2)} · (Vgs-Vth2)2 The condition for the operation of the gate region of the thin film transistor (transistor) in the saturation region is Vds as the source of the drain The voltage between the poles is generally given by > (Formula 3)

I Vds I > I Vgs-Vth I Here, since the transistor 271a and the transistor 271b are formed close to the inside of a minute pixel, approximately #1=//2 and Coxl=Cox2, if not specifically noted, Said Vth 1 = Vth2. As a result, at this time, it is easy to derive the following formula from (Formula 丄) and (Formula 2). (Formula 4)

Idrv/Iw=(W2/L2)/(Wl/L 1) The point to note here is that in (Formula 1) and (Formula 2), the values of #, Cox, and Vth are generally in each pixel, each product, or There are variations in each manufacturing lot, but (Formula 4) does not include this special parameter 'so the value of Idrv/Iw does not depend on these changes. Assume that W1=W2, L1=L2, Idrv/Iw=l, that is, Iw and Idrv are the same value. That is, the driving current Idd flowing into the EL element 15 is correctly the same as the signal current IW without being limited to the characteristic variation of the transistor, and as a result, the luminance of the EL element 15 can be accurately controlled. 94992-961016.doc -25- 1295792 As above, since Vth1 of the driving transistor 27la is substantially the same as Vth2 of the driving transistor 27 1b, if the gates of the two transistors are at the common potential, the gate is applied. When the signal voltage is level, both the transistor 27 ia and the transistor 27 lb should be in a non-conducting state. However, in reality, Vth2 becomes lower than Vthl due to factors such as parameter variation. At this time, the leakage current of the subcritical level flows into the driving transistor 27lb, so that the El element 15 exhibits microluminescence. Due to this micro-luminescence, the contrast of the kneading surface is lowered, which detracts from the display characteristics. In the present invention, the threshold voltage Vth2 of the driving transistor 27lb is set to be not lower than the threshold voltage Vth1 of the corresponding driving transistor 271a in the pixel. For example, the gate length L2 of the transistor 271b is longer than the gate length L1 of the transistor 271a, and even if the process parameters of the thin film transistors are changed, Vth2 is not lower than Vth1. Thereby, a small current leakage can be suppressed. The above matters also apply to the relationship between the transistor 271a of Fig. 1 and the transistor lie. As shown in Fig. 27, in addition to the driving transistor 271a through which the signal current flows, and the driving transistor 271b for controlling the driving current of the light-emitting elements formed by the EL element 15 and the like, the configuration further includes: by the gate signal The gate 11a is controlled to connect or disconnect the pixel circuit and the data line data into the transistor 11b, and the gate of the transistor 271a is controlled during the writing period by the control of the gate signal line 7a2. The switching transistor transistor for short-circuiting, the capacitor c 19 for maintaining the gate-source voltage of the transistor 27 la after the end of writing, the EL element 15 as a light-emitting element, and the like. In Fig. 27, the transistors ilb and Uc are composed of N-channel M〇s (NMC)S), and other electro-crystalline systems are composed of p-channel M〇s (PM〇s), but this is an example, 94992-961016. Doc •26- 1295792 does not necessarily need to follow this. Lei Xuan C will be a pot -3⁄4. J.0, ? Electricity L1 shows the common side 'sub-connected to the transistor 271 a The other side of the gate is connected to Vdd (power supply potential), but not limited to Vdd, any certain The potential is also available. The cathode (Cath〇de) of the EL element 15 is connected to the ground potential. Therefore, the above matters are of course applicable to Figure 1 and the like. Furthermore, the Vdd voltage of FIG. 1 and the like should be lower than the closing voltage of the transistor 27 lb (when the transistor is a P channel), specifically, Vgh (the closing voltage of the gate) should be at least higher than Vdd-0.5 (V). . If it is lower than this, the shutdown leakage of the transistor will occur, and the uneven illumination of the laser annealing becomes apparent. Also, it should be lower than vdd+4(v). If it is too high, it will increase the power leakage. Therefore, the gate closing voltage (Vgh, that is, the voltage side close to the power supply voltage) should be -0.5 (V) or more and +4 (v) or less. Preferably, the power supply voltage (Vdd in Fig. 1) should be above 0 (V) and below +2 (v). In summary, the turn-off voltage of the transistor applied to the gate # line is sufficiently turned off. When the transistor is in the N channel, Vgl becomes the off voltage, and therefore vgl is in the range of -4 (v) or more and 0·5 (ν) or less for the gnd voltage. And it is better in the range of _2 (V) or more and 〇 (V). The above description is directed to the pixel configuration of the current program of Fig. 1, but is not limited thereto. It is of course also applicable to the pixel configuration of the voltage program. Furthermore, the Vt offset cancellation of the voltage program should be individually compensated for each r, g, and B. The driving transistor 271b is connected to the gate electrode at a voltage level held by the capacitor 19, and has a driving current according to the current level thereof, and flows into the EL element 15 via the channel. The gate of transistor 27 la and the gate of transistor 271b are directly connected to form a current mirror circuit, and the current level of signal current IW is proportional to the current level of the drive current. 94992-961016.doc -27- 1295792 The transistor 271b operates in a saturation region, and a driving current corresponding to the difference between the voltage level applied to the gate thereof and the threshold voltage flows into the E1 element 15. The transistor 271 b is set such that its threshold voltage is not lower than the corresponding voltage of the corresponding transistor 271 & Specifically, the transistor 27113 is set such that its gate length is not shorter than the gate length of the transistor 271a, or the transistor 271b may have its gate insulating film not thinner than the gate of the corresponding transistor 271 & Set with an insulating film. Alternatively, the transistor 271b can also adjust the impurity concentration of the channel implanted therein so that the threshold voltage is not lower than the threshold voltage of the corresponding transistor 271 & Assuming that the threshold voltages of the transistors 271a and 271b are the same, if the signal voltage of the cutoff level is applied to the gate of the commonly connected transistor, both the transistor 271a and the transistor 271b should be turned off. . However, in practice, there are slight variations in the process parameters in the pixel, and the threshold voltage of the transistor 271b may become lower than the threshold voltage of the transistor 271 & At this time, even if the signal voltage is below the cutoff level, the weak current due to the subcritical level flows into the driving transistor 271b, so that the el element 15 is slightly illuminated, and the face-to-face ratio is lowered. Therefore, the gate of the transistor "" is made longer than the gate of the transistor 271a. Thereby, even if the process parameter of the transistor changes within the pixel, the threshold voltage of the transistor (4) is not lower than the threshold voltage of the transistor 27 la. In the short channel effect region A where the gate length L is relatively short, as the gate length B increases, the 'Vth rises. On the other hand, in the case where the extremely long L is relatively large, the suppression ^ or B ' is substantially constant regardless of the length L. By utilizing the characteristics, the gate length of the electrode body 271b is longer than that of the transistor. For example, • Transistor 94992-961016.doc 1295792 When the gate length of 27la is 7 μηι, the gate length of the transistor 27 lb is set to i〇. The gate length of the transistor 271a belongs to the short channel effect region Α, and on the other hand, the gate length of the transistor 27 lb is the suppression region]. Thereby, the short channel effect of the transistor 271b can be suppressed, and the threshold voltage drop caused by the variation of the process parameters can be suppressed. With the above, it is possible to suppress the leakage current which flows into the subcritical level of the transistor 271b, and suppress the microluminescence of the EL element 15 to contribute to the improvement of the contrast. The EL element 15' described in Fig. 1, Fig. 2, Fig. 2, and the like thus produced is continuously driven at a constant current density of 1 mA mA/cm 2 . The ^^ structure was confirmed to emit light at 7.0 V, 200 cd/cm2 green (luminous maximum wavelength Amax = 460 nm). The blue light-emitting portion obtains a luminance of 1 〇〇 (^^2, a color coordinate of χ=0·129, y=0·105, a luminance of 200 cd/cm2 for the green light-emitting portion, and a color coordinate of χ=〇·340 , y=〇625 illuminating color, the red illuminating part obtains a brightness of 100 cd/cm2, and the color coordinates are χ=〇.649, 丫=〇.338. If the aperture ratio is increased, the light utilization efficiency increases. In order to increase the aperture ratio, it is important to develop an aperture ratio in a full-color organic EL display panel. In order to increase the aperture ratio, it is only necessary to reduce the area of the transistor that shields light from the organic EL layer. In the amorphous germanium, the low-temperature polycrystalline Si-crystal has a performance of 10 to 1 times, and the current supply capability is high, so that the size of the transistor can be greatly reduced. Therefore, in the organic display panel, low-temperature polysilicon technology should be used. The high-temperature polysilicon technology is used to fabricate the pixel transistor and the peripheral driving circuit. Of course, it is also formed by the amorphous germanium technology, but the pixel aperture ratio of 94092-961016.doc -29- 1295792 becomes small. The gate is formed on the glass substrate 71. Driver circuit 12 or The driver circuit such as the pole driver circuit 14 can reduce the resistance which is particularly problematic in the current-driven organic EL display panel. In addition to eliminating the connection resistance of the TCp, the phase pull-out line from the electrode becomes shorter in the case of the TCP connection. 3 mm, the wiring resistance becomes small, and there is an advantage that the material cost is not required for the TCp connection process. Next, the EL display panel or the display device according to the present invention will be described. Fig. 6 is a description centering on the circuit of the EL display device. The pixels 16 are arranged or formed in a matrix, and the source driver circuit 14 is connected to each of the pixels 16 to output a current program for each pixel. The output segment of the source driver circuit 14 forms the number of bits corresponding to the image signal. Current mirror circuit (to be described later). For example, if 64 gray scales, 63 current mirror circuits are formed on each source signal line 'by selecting the number of such current mirror circuits, the desired current can be applied to the source The signal line 18 is formed. Further, the minimum output current of one unit transistor of one current mirror circuit is set to 10 ΠΑ or more and 50 nA or less. In order to ensure the accuracy of the transistor constituting the current mirror circuit in the source driver IC 14, the minimum output current of the current mirror circuit should be I5 nA or more and 35 nA or less. Also, a precharge or discharge circuit is built in, which is a source signal. The charge of the coil 8 is forcibly discharged or charged. Since the threshold value of the EL element 15 is different in RGB, the voltage (current) output value of the precharge or discharge circuit for forcibly discharging or charging the source signal line 18 is suitable. The R, G, and B are independently set to constitute 0. 9499-961016.doc -30- 1295792 The pixel structure described above is used for the following (10) salt array structure, panel structure, and the like. Of course, the configuration, method, and apparatus described below are suitable. Further, the following description of the method and the device is of course applied to the description of the configuration and the like. Pixel structure, array structure, panel @12 system built-in gate signal line (10) offset register circuit a and idle signal line m offset register circuit circuit circuit 61 is positive and negative The phase signal (: :) and the start pulse (STx) are controlled. In addition, the output of the control gate, the non-output enable (10) 胤 signal, and the up-and-down reverse direction (UPDWM) signal should be added. Others should set the output terminal, etc., and confirm that the start pulse is shifted toward the offset register and output. Furthermore, the offset timing of the offset register is controlled by a control signal from the controller (3). Moreover, a level shift circuit for level shifting of external data is built in, and a check circuit is built in. Fig. 8 is a view showing the configuration of a signal and a voltage supply of a display device of the present invention or a configuration of a display device. The signal (power supply wiring, data wiring, etc.) supplied from the control IC 81 to the source driver circuit 14a is supplied via the flexible substrate 84. In Fig. 8, the control signal of the gate driver 12 is generated by the control IC, and is applied to the gate driver 12 once the source driver 14 is level-shifted. Since the driving voltage of the source driver 14 is 4 to 8 (V), the control signal of the 3·3 (ν) amplitude outputted from the control IC 81 can be converted into the 5 (V) amplitude accepted by the gate driver. The following describes the driving method relating to the present invention. The present invention is dedicated to brightness adjustment driving of an organic EL panel drive. The organic EL element emits light in accordance with the charge and Vdd stored in the storage capacitor 19 of 94992-961016.doc -31 - 1295792 in proportion to the amount of current flowing into the driving transistor 11a. Therefore, as shown in Fig. 12, the total current flowing into the panel is linear with the brightness of the panel. As shown in Fig. 24, the voltage vdd for flowing a current into the organic EL panel is supplied from the battery 241. This battery 241 has a capacity limitation, and particularly in the case of a small module, the amount of current that can flow out becomes small. Assume that as shown in Fig. 25, the battery 241 can only flow out of 50% of the power consumed by the organic EL panel. Here, if the relationship between the brightness emitted by the organic EL element (the total white display is 100 G/〇) and the electric power is determined by the straight line 251 shown in 251, the maximum current amount that the battery can flow out in the region where the brightness is high is exceeded. Therefore, fear of destroying the battery. On the contrary, as shown in 252, if the amount of current flowing when the maximum illumination of the organic EL panel is the same as the maximum amount of current that can be discharged from the battery 241, and the relationship between the brightness and the electric power is determined, the current cannot flow in the low-luminance portion. . In general, if the image data is set to 1〇〇% for the full white display state, the vicinity of 3〇% is called more. If the relationship between the brightness and the amount of current indicated by 252 is set, the current will not flow in the area where there is much image data, and it will become a non-bright image. Therefore, in the present invention, as shown in FIG. 26, a specific input data is set, and according to the data proposal, the driving of the current flowing into the organic EL panel is adjusted, and the current value is suppressed in a region that may exceed the critical value of the battery. A driving method that increases the amount of current in a region where current does not flow. When this driving method is implemented, the relationship between the brightness and the current amount of the organic EL panel becomes 282. Even if the capacity of the battery is limited, it is possible to flow a current in a region where there is a large amount of image data, and to produce an image with a good margin. The content of the present invention is a combination of two driving methods, and the side driving method and the applicable circuit configuration will be described below. The first driver 94092-961016.doc -32- 1295792 is the same as the conventional driving method, and the input image data from the outside and the brightness of the screen using the self-issuing device or the self-illuminating device The relationship between the amount of current between the anode electrode and the cathode electrode is 1:1, that is, the value of the current obtained for the i input image data! The value of the pre-mosquito' causes each display pixel to emit light in accordance with the first brightness from the external input image signal. x, which are in a proportional relationship, ideally proportional to a linear shape. In the present invention, the case where it is applied to the low-gradation side (black display side) driving is specifically described. On the other hand, the second driving method is based on the external input image data and the brightness of the surface of the display device using the self-luminous element, or the relationship between the amount of current flowing into the anode electrode and the cathode electrode of the self-luminous element is not 1: 1 And 1 determines the amount of current that takes into account the distribution of the input image data of Zhou Wei, that is, determines a value set by the variable value. Therefore, the first driving method different from the above is not limited to the proportional relationship of the linear shapes, and is often a non-linear relationship. At this time, each of the display pixels is caused to emit light by the second brightness, and the second brightness is suppressed by the first brightness of the input image signal from the outside at a specific ratio. Therefore, unlike the previous first drive, it is not limited to the proportional relationship of the linear shapes, and more often becomes a non-linear relationship. In the second driving method, the value of the current amount is first obtained by multiplying a certain constant (1 or less) when a current amount when the first driving method is applied to the image data input from the outside is i, The amount of current. The constant value is determined each time according to the distribution of the surrounding input image signals. Further, the driving method is characterized in that, as described above, since a large amount of current flows in a region where a large amount of image data is required, if the maximum input data is not subjected to the suppression processing 94092-961016.doc -33 - 1295792 or The electric current is regarded as 丨, and the electric power or the current amount is adjusted so that the electric power value X becomes 0.2$χ$0·6 in the region where the second drive is applied. Furthermore, the circuit for setting the second driving is provided with a switching means for controlling the cutting of the second driving means so that the driving method of the present invention can be performed when the second driving means is turned on, and when the second driving means is turned off, It is interchangeable with previous driving methods. As a method of adjusting the current value, two methods are proposed. One is to reduce the amount of current flowing into the source L-line 18, and to adjust the amount of current flowing into the organic EL element. However, this method must reduce the amount of current flowing into the source winding 18 while suppressing the amount of current. As described above, the organic EL element emits light in accordance with the charge stored in the storage capacitor 19. In order to properly emit the input data, it is necessary to store the charge which causes the correct current value to flow into the storage capacitor 19. In fact, there is a floating capacitor 45 1 in the source signal line 18, in order to change the voltage of the primary pole 仏 line from V2 to v b, the time Δ τ of the electric power of the floating capacitor must be pulled out. △ Q (charge of floating capacitor) = ι (current of source 2 source 仏 line) xAT = C (floating capacitance value) > Δ V. If you want to use salty water and electricity: the value 1 'will not store the correct charge in the storage capacitor 19, and, *...7, "gas value" will be difficult to express gray scale. If you want to express grayscale in grayscale, you must The difference between the current value of the black light and the current value of the white color will be divided into 1024 equal parts. 囡—u this right reduces the current value of white, and the current change per 1 gray level becomes smaller, in order to perform The accuracy of gray scale becomes high, which is difficult to achieve. First, the description of the ancient M & 'in order to judge the display data of the image. The display data is the current consumption of the image data from the red-curved plate (flowing into the anode electrode and the cathode electrode 94092-961016) .doc -34- 1295792 current) derived. In Taixu ^ Shi Ben Mao Ming, the display data in %, 100% is the maximum value of the display material 'that is, all pixels in the state of the highest gray light' 〇 % is the state in which all pixels are illuminated at the lowest gray level. When the image of the image is large on the whole, the sum of the image data becomes larger. For example, when the white gloss is displayed in 64 gradations, the image data is 63, so the number of pixels of the face 50 x63 is the image The sum of the materials. In the white window of ι/ι〇〇, the white display is displayed in the white display of the maximum brightness. The sum of the image data is the number of pixels in the screen 50.../just) ^(The maximum value of the data and the maximum In the present invention, the sum of the pre-image data or the value of the consumption motor of the screen is obtained, and based on the sum or value, the driving of the amount of current flowing between the anode electrode and the cathode electrode of the self-luminous element is suppressed. Although the sum of the image data is obtained, it is not limited thereto. For example, it is also possible to obtain the average level of the image data, and if the analog signal is used, the analog image signal is filtered by the capacitor. The average level can be obtained. For the analog image signal, the DC level is extracted through the filter, and the DC level is AD-converted as the sum of the image data. At this time, the image data can also be called APL. In the present invention, there is a case where the display data is written as input data, but this is a synonym. Also, it is not necessary to add all the data constituting the image of the screen, and the i/w of the screen can also be selected (w ratio 1 Big value) The sum of the selected data. The data and / maximum value are synonymous with the ratio of the displayed data (input data). If the data and / maximum value is 1, the input data is 100% (basically the maximum white gloss display). The data and / maximum value are 〇, and the input data is (substantially 94992-961016.doc -35- 1295792 complete black gloss display). The material and / maximum value are obtained from the sum of the image data. Input image data When y, u, and v are used, they can also be obtained from the γ (luminance) signal. However, in the case of the panel, since the luminous efficiencies in R, G, and B are different, the value obtained from the γ signal does not become power consumption. Therefore, in the case of γ, U, and v, it is also necessary to temporarily convert into R, G, and β signals, and calculate the current consumption (power consumption) by multiplying the current by the converted factor according to R, G, and B. However, it is also conceivable to easily obtain the current consumption from the γ signal to make circuit processing easy. In order to obtain the ratio of the displayed data with good precision, the calculation can be performed. The so-called calculation system includes addition, subtraction, multiplication, and division. Further, there is a method in which the current value flowing into the organic EL panel is measured by an external circuit, and the judgment is made by feedback. Similarly, data obtained by built-in thermistors or thermoelectric equivalent temperature sensors or photo sensors in the organic rainbow panel can also be utilized. The display data is converted by the current flowing into the panel, that is, the amount of current flowing between the anode electrode and the cathode electrode of the self-luminous element. Because the luminous efficiency of B is not good due to the display panel in the el, if the display of the sea is displayed, the power consumption will increase the maximum value to the maximum value of the power supply capacity, and the so-called power supply and the added value of the image data are not simple. Instead, the image data is converted into a current consumption. Therefore, the lighting rate is also obtained from the current used for each image of the maximum current. The second system converts the current value J flowing into the source signal line as it is to the horizontal scanning line number (lighting rate) of the picture lighting to control the brightness. The organic el panel controls the opening time of the transistor lid to control the lighting time in one of the horizontal scanning lines 94992-961016.doc -36 - 1295792. As shown in Fig. 14, when the gate driver 12 is controlled to perform driving for lighting only during the 1/N period in the frame, the brightness is 1/N of the brightness of the case where all the horizontal scanning lines are constantly lit. The brightness can be adjusted by this method. In this method, since the luminance is controlled during the light emission, even if the technical illumination ΐ ' does not change the accuracy required for the current value flowing into the source signal line for realizing the gradation, it is easy to realize the gradation expression. Therefore, the present invention proposes a driving method for suppressing the current flowing into the organic EL panel by controlling the lighting rate. The relationship between the lamp-free rate and the input data is not limited to the proportional relationship, as shown in Figure 29, and can also be a curve or a broken line. If you consider the situation where the high light-emitting rate is maintained for a certain period of time, then the pattern is reduced according to the data, and the brightness of the general image data is more than 30% (the overall white is displayed as ι00%). Live' can be said to be effective. It is assumed that the capacity of the battery 241 can flow into the organic EL panel at a maximum current of 50°/❶, and the battery can be prevented from being destroyed even if the input data causes the maximum lighting rate to reach a maximum of 50%. Further, it is not necessary to control the brightness to completely turn off the transistor 1 Id , and it is possible to control the brightness while a small amount of current flows into the transistor lid and the organic EL element 15 is slightly illuminated. Further, the non-light-emitting or micro-light-emitting period causes the organic EL element 15 to be non-light-emitting or micro-light-emitting, and is not limited to those produced by the opening and closing of the transistor 1 Id. For example, as shown in Fig. 132 or Fig. 133, even without the configuration of the transistor lid, a non-light-emitting or micro-light-emitting period can be generated by raising or lowering the anode voltage or the cathode voltage. Further, the present invention controls the current applied to the organic EL element 15, and the circuit configuration shown in Fig. 76 94992-961016.doc - 37 - 1295792 is also the same as the control 76lg. Further, the non-light-emitting portion for controlling the brightness is not limited to the horizontal scanning line, that is, not limited to the pixel column direction, and the source driver 14 can be controlled to perform non-light-emitting or micro-light-emitting periods in the pixel column direction to control the brightness. By making a micro-lighting or non-light-emitting period, a micro-lighting or a non-light-emitting display can be performed on the stamp = direction or the pixel row direction in the displayed image. Adding this deuterated or non-illuminated display to the display image is called black insertion.

Also, the input data should be between the minimum and maximum, and the engraving of 2 to the 11th power. If you are completely black, if it is 〇, the full white light is 256 (2 to the 8th power). In order to calculate the change in the lighting rate, in order to obtain the amount of change, it is necessary to use the light input: divide by the maximum lighting rate and the minimum lighting rate. In the semiconductor design, the circuit of the input and subtraction circuit is extremely large in the circuit configuration. If the overall white display is 2 nth power, the slope is only to make the difference between the maximum lighting rate and the minimum = lamp rate 2 The number is offset by 8 bits, so if it is considered from the viewpoint of semiconductor design, it is not necessary to be incorporated into the circuit, and the circuit design becomes very easy. As in the case of 291, when the maximum light-emitting rate is maintained for a certain period of time and the waveform of the party light rate is gradually reduced, the light-emitting rate of the maximum of the input data as shown in Fig. 3() is: The maximum waveform is a straight line with a point U. If the slope is X, the slope is only 2χ during the period from 2 to 人, so that it can be compared with the linear ice phase X # & With this configuration, only the slope of the straight line type is obtained, and the curve of the line type is lowered, and the page is re-evaluated by the gradient of the line, and the circuit gauge is not increased: Made into a variety of broken line curves. This has the advantage of making the circuit scale smaller in circuit design. Private 94992-9610l6.doc -38 - 1295792 Next, in Figure 55, explain why?目士邮心 ^ Bureau ί realizes the circuit structure of this driver. First, the color data of the job source is initially input into the 551. The same data is input to the source driver 14 via image processing such as r processing. Rgb color information, but not limited to jobs. It is also possible to consider YUVI = temperature data or brightness data obtained by the aforementioned thermistor or photo sensor. After expanding the data in 551, the data is entered into the module w for collecting data. The information expansion on (5) will be described later. At 552, the data is first input to the adder 552a, but in the case where the data does not come often, it may be an indefinite material other than the image data. Therefore, the adder can decide whether to add or not by the enable signal (DE) and the clock (CLK) of whether the data arrives. However, in order to feed the circuit in which the image material* is input in advance, an enable signal is not required. The added data is stored in the 55 hole of the scratchpad, and is latched by the vertical sync signal (VD) at the "仏", and the upper 8 bits of the data of the register (2 digits) are output. The size of the register is not specified. The larger the size of the register, the larger the circuit scale, but the accuracy of the added data is improved. Moreover, the output data is not fixed at 8 bits. When the brightness rate control is to be performed in a finer range, the output data is 9 bits. Above the yuan, if the accuracy is not necessary, it is no problem under 7 bits. The maximum value of the output value is the scale of the input data. When the maximum value of the output 8-bit is 100, the input data is judged by 100 division. In order to reduce the circuit scale, the input data should be engraved by 2 η power. Therefore, in 551, in order to easily divide the data obtained between 1F into 255 equal parts, data expansion is performed. In the case where the output value is at most 1 〇〇, the input data itself is input at 2 55 times in 551, and the maximum value of the output value can be 255 (if 〇 is included, there are 256 (2 to 8 powers)) 94992-961016.doc -39- 1295792 The value of the output octet is input to the module 555 for calculating the lighting rate. The value input at 555 is calculated and output as the lighting rate control value 556. The lighting rate control value 556 is input to the gate control area. Block 553 'gate control block 553 is initialized in synchronization with VD and has a counter 554 that is up by the horizontal sync signal (hd). Figure 56 shows the gate with a light rate control value of 556 of 15. The time of the pole control block 553. When the counter 554 is 0, STwm (high) (turns on the switching transistor lib, 11c). The claw system controls the start pulse of the gate signal line m, and the switch is turned on/off by 17a. Crystals 11b, Uc. Further, when the counter 554 is 1, ST4L0W (low), and ST2 is HI. ST2 is used to control the start pulse of the gate signal line 17b, and the switch transistor 13 is turned on/off by 17b. The length of the HI period of ST2 is directly related to the illumination time of the organic component 1]. Therefore, when the value of the illumination rate control signal is the same as the value of the counter 554, if the ST2 becomes LOW, the illumination rate control signal can be used. Value adjustment organic £1^ The amount of illumination of the piece 15. The lighting rate control 556 is, the lighting rate is 1/255, so the amount of light is 1/255. Thereby the brightness can be controlled. The counter value of making ST1 and 2 HI is not fixed at 〇, i, and may take into account the delay of image data. In Fig. 55, the lighting rate control signal has an 8-bit value, as shown in Fig. 57, the lighting rate control signal is the i-bit of the HI period having the lighting rate inside the 552. The signal line of the element. In the case of Fig. 57, the signal line of the ST2 and the lighting rate control signal line can be logically operated to control the lighting time. Further, the switching transistors 丨 lb, 11 c, 11 d ' constructed as end-view pixels also have the logic of inverting the gate signal lines. Next, a method of delaying the illumination rate of 94992-961016.doc -40 - 1295792 at the time of driving the present invention is proposed. As shown in Fig. 38, if the input data is greatly degraded for the time axis 〇' 1' 2'), the lighting rate will vary greatly. If this becomes the case, the redundancy within the face will change frequently and cause flashing. Therefore, the difference between the current lighting rate and the lighting rate of the predetermined change of the secondary tape is shown in Fig. 39, so that the difference % is changed to ease the ratio of the change. If the expression is 'the luminous rate of time t is γ(1), and the light-free rate of the input data of time (1) is Y—(1), then Y(t + Ι)=γ(1)+ (γ - (t)- Y(1))/(4)G)...(5Wx) When the lighting rate is changed, if the difference in lighting rate is large, the amount of change becomes larger. The difference is small, and the amount of change becomes small. Therefore, if s is too large, the lighting rate changes. The required time becomes longer. ^ Figure 59 shows the relationship between the required light and the s when the lighting rate is moved from G to _. When the image is projected at a frequency of 60 Hz, the lighting rate is moved from 0% to 100%. s=32' requires about 200 buildings, so it takes about 3 seconds. If the time required for the change exceeds this, the brightness change does not seem smooth. Also, if the price is too small, it will not improve the flicker. In circuit design. Since the data is displayed in 2 digits, the calculation circuit requires a large amount of logic, which cannot be realized in reality. When the calculation is performed by the η power of 2, the left end of the data marked with 2 digits is taken as the 咼 position. If the right end is the lowest bit, as long as the η bit is shifted to the right, the same effect as the division is obtained, so the circuit configuration becomes very From the above point of view, s should be the second-order power. Figure 134 shows the change in the lighting rate from the full black display state to the white-white display state. The result of the review is s=2, the improvement effect Small, but when s = 4, the flash is improved. Moreover, if it exceeds s = 256, the change takes too much time, so the suppression function cannot be exerted. From the above, the present invention sets the range of s to 94092-961016.doc -41 - 1295792 256. Moreover, 32 is particularly preferable. Thereby, good display without flicker can be obtained. Furthermore, in addition to the circuit design, 3 is not limited to the nth power of 2. Further, the equation (5) is > (1) _ Υ (1)) / s numerator (γ (1)) becomes "times, the range of s is also r times. s is not always possible, but also in areas with high lighting rate, because sb is less, so s is less than Method 4. Therefore, it is also possible to change s in areas with high lighting rate and low areas. For example, when the lighting rate is above 5〇%, it should be controlled by 2 Ss$16, and the lighting rate is 5〇%. In the following, it should be controlled by 4gs^32. Also, if you want to change the lighting rate and increase the speed when changing the speed' It is also effective to change the s value by the magnitude relationship of Y (t) and Y (t). The circuit configuration of the driving method for delaying the change of the lighting rate is shown in Fig. 58 as follows, and the data output from 551 is added by the adder 5 52a. And the error is stored in the register 55. The value of the octet outputted by the operation module operation and the VD is synchronized, and the brightness control value (t) is derived, and γ / (1) is input to the subtraction module 582. In the module 582, the lighting rate control value γ(1) obtained by the register 583 holding the current lighting rate control value and the lighting rate control value γ derived from the current input data, (1) are subtracted. Two differences s(t) are produced. Next, 'S(t) performs the division processing in 584 by inputting the s value. As described above, since the arithmetic processing requires complicated logic, S(t) can be shifted by η bits toward the least significant bit (LSB) side by setting the input s value to the nth power of 2, thereby performing division. The S(t) system after the division and the current lighting rate t value Y(t)' held in the register 583 are added by the addition module 585. The value added at 585 becomes the luminance control value 556, which is input to the gate control block 553. Moreover, the lighting rate of 94992-961016.doc -42 - 1295792 is controlled by the input value to the temporary storage ^83 to be reflected in the secondary building. In the case of the method of J and the method of 58, when s(1) is shifted by n bits, only the offset is discarded, and there is a problem in accuracy. Specifically, in the case of Η, since n = 3 ′, the offset is 3 bits, but when s(1) is about the following value, if it is shifted by 3 bits toward the LSB side, it becomes 〇. As a method of avoiding, both s(1) and · are shifted by n bits in advance toward the most significant bit (10) B), and at the time of output, the output data is shifted by η bits toward the LSB side and rotated. Alternatively, as shown in Fig. 61, the initial value Υ(9) is shifted by η bits toward the deletion side and stored in the register M3. The data at the time when s(t) has been added is stored in the register 583, and the output data is shifted by n bits toward the LSB side and output. The S(1) added after the initial value is shifted to the listening side by η bits is the same as the offset by n bits toward the LSB side, and the data stored in the register 583 is discarded because there is no offset by the offset. Therefore, the accuracy is improved. Fig. 40 shows the change in the lighting rate when the input data is shifted from the minimum to the maximum. If the lighting rate is changed in the manner previously described, the lighting rate will change as a curve. However, at this time, in the area indicated by the operation, the power supply is exceeded because the limit value of the power supply capacity is exceeded. Therefore, as shown in Fig. 41, the method of changing the lighting rate and reducing the daily change is proposed. If the lighting rate is low = area, if the lighting rate changes greatly, it will appear to be flashing, but in the area of the lighting rate, even if the lighting rate is greatly changed, it will not appear to be flashing. This is due to the fact that the ratio of the black display (non-display portion) in the contraction screen is large in the region where the lighting rate is low. In areas where the ratio of the black display portion is small and the lighting rate is high, even if the lighting rate is greatly reduced, the image quality is not affected. Therefore, when the lighting rate is above 5〇%, the γ calculated from the input data and the less than 5〇% of 94992-961016.doc -43 - 1295792 are used to reduce the rate of non-use to 5〇〇. /. . The driving method is to turn on the light..., and the limit value of the power supply capacity is larger than 5〇% to suppress the van Gogh light rate in the limit according to the limit capacity w 氐 to 50%, preferably 75 capacity is not full Even reduce the lighting rate to 5. %= The limit capacity of the source, but from the point of view of flashing, it is not appropriate to == 50% of the lighting rate. If the method is lowered, the lighting rate is judged to change after the input data. Therefore, the limit value of the power supply capacity may be exceeded between frames. For example, as shown in Figure 42, the right input data = the brightness data of the image of the organic panel, if the display is continuous for a short time, 'because the input data is small, the lighting rate becomes the most comprehensive white display. This frame will maintain the maximum lighting rate and become a full white display. At this time, the amount of current flowing into the organic EL panel is located in the area indicated by 421, exceeding the limit capacity of the power source. In order to avoid this phenomenon, there are two methods. One is a frame memory inside the circuit. If the image data is stored in the frame memory for a while, and then the composition of the user, the user, and the member are displayed, the lighting rate can be lowered before the white display. However, if there is a frame memory in the circuit, there is a disadvantage that the circuit scale becomes large. Therefore, a method of avoiding this phenomenon without using frame memory is proposed. As shown in Fig. 43, a signal line 432 is applied to the gate signal line 431 of the input gate driver 12, and the two signal lines are logically operated by AND. Thereby, when the signal line 432 is at HI (high), according to the gate signal line 431, the transistor lid of the organic EL panel is turned on/off, and when the signal line 432 is low (low), it is not limited to the gate signal line 431. The transistor lid of the organic EL panel is turned off. 94992-961016.doc -44- 1295792 Of course, it is no problem to perform logical operations outside of AND and change the combination of two signal lines. Here, when the logic operation is performed by AND, and the gate signal line 丨7 is LOW, the transistor 11d of the organic EL panel is turned off. First, the threshold value of the input data is calculated from the xenon lamp rate. Assuming that the lighting rate is i 〇〇%, the limit value of the power supply capacity is 50%, and the input data is at the limit of 5〇%. When the lighting rate is 7〇%, the input data is 50%, and the input data is at the limit of 71%. The input data is at a point in time when the threshold value is reached, and the signal line 432 is lowered to LOW. As a result, the gate signal line 17 becomes L 〇 w, and the crystal crystal 1 Id of the organic EL panel is turned off. At this time, a change of the display area is shown in FIG. At this point, if the threshold value is reached, the signal line 432 becomes L〇w, and the gate signal line of the transistor lid of the first line is operated. "Become a sputum, whereby the first line becomes non-lighting, and the line continues to be non-lighting until 17a (1) becomes HI. After the first line becomes non-lighting, every 1H, 17b(2), 17b(3)... sequentially becomes L〇w, and the second line and the third line are sequentially turned off. If this is shown in the figure, the order is 441, 442, and 443, and the lines are The xenon time does not change. Therefore, even if this process is performed on the frame, the image will not be affected. By this method, the current can be suppressed without using the block memory so as not to exceed the limit capacity of the power supply. As shown in FIG. 19, the display of the present invention can adjust the brightness by displaying the area of illumination in one frame. As shown in FIG. 13, if the number of horizontal scanning lines of the image display area is set to S, it is bright between frames. When the display area of the lamp is set to n, the shell of the display area is N/S. As previously described, the brightness adjustment of the display area of the method can be controlled by the offset register circuit 61 of the idle driver circuit 12. 94992-961016.doc -45- 1295792 is easy to implement. However, this method can only be used in the S phase. The brightness of the entire display area is shown in Fig. 31. The brightness of the display area is changed when n of the display area of the redundant lamp is changed. Since the brightness is adjusted by the change of the number of scanning lines of light > 1, the brightness changes as shown in the figure. When the brightness is adjusted to a small extent, it does not pose a problem. However, when the adjustment range of the brightness is large, if the adjustment method is adopted, the brightness change when N is changed becomes large, and it is difficult to smoothly change the brightness. Therefore, as shown in FIG. As shown, two signal lines 62a and 62b are disposed in the gate driver 12, and the two signal lines 62a and 62b are connected to the gate control signal line 64 and the OR circuit 65 connected to the offset register. The output of the circuit 65 is connected to the output signal buffer 63 and output to the gate signal line 17. As shown in Fig. 28, the gate signal line 17 becomes only the signal lines 62 and 64. When any of them is HI, HI is output. Thereby, when the transistors 11b and lid are turned on (the gate signal line 17 is L〇W output), the signal line 62 is output to HI for the gate. The signal line 17 can perform HI output, turning off the transistors Ub, nd. Furthermore, the present invention is not limited to the combination of the signal line and the OR circuit, and the gate signal line 17 is changed by changing the signal line ,, so that the AND circuit, the nand circuit, and the NOR circuit are replaced by the 〇R circuit. As shown in Fig. 32, by adjusting the output period of the signal line 62b2HI, the illumination time of the EL element 15 is adjusted. If attention is paid to the case of a component, the number of illumination lines is N, and the frame is illuminated. During the N horizontal scanning period (h), the light is turned on. If the output period of the signal line 6213 in the horizontal period (111) is set to M (/〇, the lighting time between the two buildings is reduced ΜχΝ (μ ). In the figure % table 94992-961016.doc -46 - 1295792 does not change the redundancy at this time. N = N 〆 and Ν = ΝΊ (the brightness between turns is expressed by the slope ΜΧ ,, whereby the stepwise brightness change of Fig. 31 can be linearly changed. The drawing signal line 62b is once performed at 1 于此 in this figure. The output is output, but the present invention is not limited thereto, and the processing signal line 62b may be turned into a HI processing method once every several Η periods, and any place disposed in the m during the HI output period does not pose a problem. If the brightness is adjusted between frames, for example, if the signal line 62b is output every 2 ducks, the period m of the m output seems to be 1/2. However, when this processing is performed, the signal line (four) is ordered only during the specific display period. In the case of HI output, uneven brightness may occur in the image display area. In this case, brightness unevenness can be eliminated by processing between several frames. For example, as shown in Fig. 3, the frame will be odd-numbered in each frame. When the light is turned on, the signal line 62b is displayed in the HI display method 351 & and the display method 351b in which the signal line 62b is turned into the HI when the even line is turned on. This eliminates the brightness unevenness in the display area on the look-and-feel. The present invention, the number of horizontal scanning lines of the display area In the case of S strips, in which N strips are inverted, the signal line 62 is operated to adjust the brightness only in the case of N/s^ 1/4. First, the advantages of operating the signal line 62 when N/s is 1/4 or less are explained. As described in A first, if the brightness is adjusted by the change of the number of scanning lines N of the lighting level, since the brightness changes to a step shape, the brightness greatly changes at the boundary of the change of the ^^. When the brightness of the display area is large, the human vision is hard to find. The magnitude of the change is small, but the change in the brightness of the display area is easy to find. Therefore, in the present invention, the amount of change in the brightness can be finely adjusted by adjusting the signal line 62 when the brightness of the display area changes little. 94992-961016.doc -47 · 1295792 Next, the problem of _ at 1/4 or more will be explained. As shown in Fig. 9, there is a floating capacitance Μ between the source signal line 18 and the gate signal line m. If the signal line 62b is made HI output The _ interpolar signal line (7) will simultaneously input = HI output, so as shown in Figure 36, due to the source signal line gate signal: the coupling of line 17b, the source signal line 18 changes. Due to this coupling, it cannot be stored. Capacitor 19 writes the correct voltage. Yes, bamboo ~ 疋 as shown in Figure 37, due to low current, in the low gradation part of the write, can not correct the change of the write voltage by light combination, such as the write voltage of the human voltage becomes high, The low gradation portion becomes higher than the target luminance 373, and when the 372-like write voltage is low, the low gradation portion becomes lower than the target luminance 373. According to the above, as the variable having the fine-tunable brightness & Further, n/s^i/4 is appropriate for a period in which the influence of the change in the write voltage is small due to the consumption. The above-described driving method is shown in Fig. 6A, and the driving is performed in 60. The above-described driving is performed. Pursuing a more detailed lighting rate control value, the 552c outputs 1 unit of data to make a lighting rate control value 556. If the lighting rate control value 556 is made by the (7) bit of the poor material, the data of the 1st and 24th stages can be made, and the brightness control value 556 of 8 bits can be finely controlled 4 times. However, the lighting rate can only be adjusted in the horizontal scanning line number s stage, so if S is the value of 8 bits, the lower 2 bits of the control data of 1 bit will be generated for the fine adjustment of the lighting rate. Alternatively, when driving as shown in Fig. 61 as described above, the n-bit data shifted toward the LSB side may be used for fine adjustment of the lighting rate at the time of output. Since the driving system is performed during the period in which the lighting rate is N/S S 1 /4, the lighting rate control value 556 is input between 555 and 601. The 601 series is driven at a light rate of 94992-961016.doc -48- 1295792 for N/S = 1/4. For example, the signal line of the previous jin is 601, and the 驱动 攸 攸 攸 攸 曾 曾 曾 曾 , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , ,闵+ , 屮 、, w ^ Therefore, in the output state of the signal line 02b, can be used as a full-pixel transistor

> W/1 _ Ud. In the interval of N/S = 1/4 in which no driving is performed, the output on the signal line 62b is such that the output waveform of the #唬 line 64b is reflected in 17b. When the N/SS is 1/4, the 601 series is synchronized with the HD, and the 冋 is not limited to HD. It can also be used by Han to drive 6 〇 1 dedicated transfer ^ί\Λ y ^ for reading; The 601 operates the signal line 62b by means of the input fine-tuning signal 602 and the clock (CLK) to turn off the transistor 1 Id during the finger period. As shown in the previous section, if the output period of the signal line (4) in the period of the N-line lighting period (1H) is set to μ (8), the lighting time between the buildings is reduced by MxN (8). Therefore, by calculating the data of m time and the data of 6〇2, the operation of 62b is performed to reduce the lighting time, and the lighting rate can be smoothly changed. Fig. 60 is a 601 type attached to Fig. 55, and can of course be applied to any of the circuit configurations described herein with reference to Fig. 58 or Fig. 61. Next, consider the case where the active matrix type display device constituted by the pixel shown in Fig. 46 writes a specific current value into the pixel from the source signal line. The circuit taken from the circuit of the current path of the source driver 1C 14 to the pixel is as shown in Fig. 45(a). The current I according to the gradation flows in the source driver 1C 14 as a current source 452 as an introduction current. This current is taken into the inside of the pixel 16 via the source signal line i 8 , and the current taken in flows into the driving transistor 丨丨 & In general, at the selected pixel 16, the current I flows from the EL power supply line 464 to the source driver IC 36 via the drive 94992-961016.doc -49-1295792, the transistor 111a, and the source signal line 18. If the image signal changes, the current value of the current source 452 changes, and the current flowing into the driving transistor 11a and the source signal line 亦8 also changes. At this time, the voltage of the source signal line changes according to the current-voltage characteristic of the driving transistor 11a. When the current-voltage characteristic of the driving transistor 11a is as shown in Fig. 45 (1), for example, if the current value of the current source 452 is changed from 12 to 11, the voltage of the source signal line is changed from V2 to vi. This voltage change is caused by the current of current source 452. The floating capacitor 45 exists in the source signal line 18. In order to change the source signal line voltage from V2 to V, the charge of the floating capacitor must be pulled out. The time Δ T taken for this pull-out is Δ Q (the charge of the floating capacitor) = 1 (the current flowing into the source signal line) χ Δ T = C (floating capacitance value) χ Δ v. Here, if Δ v (the amplitude of the signal line of the black display time when white is displayed) is 5 [v], c = 1 〇 pF, and 〇 l 〇 nA, Δ Τ = 50 msec is required. This is longer than 1 horizontal scanning period (75 μsec) when qcif + size (pixel number 176x220) is driven at a frame frequency of 6 Hz, so if the pixel to be displayed under the white display pixel is black, the source signal In the middle of the line current change, the switching transistor (1) that writes current into the pixel will turn off, which means that the intermediate gray level is stored in the memory, and the brightness is illuminated in the middle of white and black. The lower the gradation, the smaller the I value becomes, the more the charge becomes, the more the brightness becomes. The more pronounced the lower the gradation is, the lower the gradation is. The current of the current source 4 5 2 is 〇, and the charge of 451 is impossible. Therefore, it is difficult to pull out the problem that the signal of the floating capacitor 4 5 1 写入 is written inside the pixel. In the extreme case, the black display does not flow current and pulls out the floating capacitance. Therefore, in order to solve this problem, the source signal line 18 shown in FIG. 47 drives 94092-961016.doc -50 - 1295792 with n times pulse, which The usual n times current is applied to the usual "n time. By this driving method, the writing time to the electric device can be shortened by writing a current higher than usual. If the source signal line flows into the n-fold current, the organic ELtg device also flows into the n-fold current. Therefore, by turning the gate control signal into ah, the on-time of the TFT 11d becomes 1/n, so that the current is applied only 1/n. During the period of the organic EL element 15, the average applied current does not change.

If the size of the floating capacitor 451 is c, the voltage of the source signal line 18 is set to V, and the current flowing into the source signal line 18 is set to 1, the time required for the current value of the source signal line 18 to change is 4t=c. V/I, the current can be increased by ι times, the time required to change the current value is 1 缩, and it means that even if the floating capacitance 451 of the source line becomes 1G times, it can be changed to specific Current value. Therefore, in order to write a specific current value into a short horizontal scanning period, increasing the current value is effective. : The input current is 1G times, the output current is also (7) times, and the Brahman is 1G times. Therefore, in order to obtain a specific brightness, the ON period of the TFT 11d of FIG. 1 becomes one of the conventional ones, and the light is turned on. The rate is 1/10, to

A specific brightness is displayed. ...,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,, Larger current. However, if a large current flows into the source gentleman 柽4唬 line 1, the current value will be pixelized, and a larger current with respect to the specific current & 丄 _ ^ flows into the EL element 15. For example, the pet is programmed with a current of 10 times, and when 10 times of current flows into the EL element 15, the EL element emits light at a magnification of 1 time. In order to become a special light-emitting shell, it is sufficient to make the time of the element 15 flowing into E] 94992-961016.doc -51. 1295792 into i/io. By driving in this way, the parasitic capacitance of the source signal line 18 can be sufficiently discharged, and a specific luminance can be obtained. Further, 10 times the current value is written to the TFT 111a of the pixel (correctly, the capacitor is set to 19) The terminal voltage) makes the ON time of the EL element 15 1/1 〇, but this is an example. According to circumstances, it is also possible to write a current value of 10 times into the TFT 11a of the pixel so that the ON time of the EL element 15 is 1/5. Conversely, there is a case where the (7) times current value is written to the TFT1 la of the pixel, and the ON time of the EL element 15 is doubled. ... If this N-time drive is used, the amount of current flowing into the source signal line can be increased, so that the problem that the signal before the change to a specific brightness is written inside the pixel can be solved. For example, the gate signal line 17b is 1F in the conventional conduction period (when the current program time is ,, the normal program time is 1H, and the number of pixel columns in the EL display device is at least 10 columns or more. Therefore, even 1F, the error is 1%. The following), if it is changed from the most time-consuming grayscale 0 to grayscale 丨, the source capacitance can be changed by 75//2 as long as it has a level of 2 PF. This means that if the 2-type EL display device' frame frequency can be driven at 6 〇 hz. Further, in a large display device, when the floating capacitance (source capacitance) 451 becomes large, the source current can be made 1 time or more. In general, when the source current value is N times, the conduction period of the gate signal line 17b (TFT 11d) may be 1 F/N. Therefore, it can also be applied to a display device for televisions and monitors. However, even if the N-times drive is expressed by the same brightness, the current flowing into the pixel instantaneously becomes N times, which imposes a great burden on the organic component. Therefore, the proposal adopts the method of controlling the lighting rate according to the input data of the invention 94992-961016.doc -52-1295792 method to display the low brightness portion of the image, controlling the lighting rate and flowing into the source ^ & ice 18 In the motor, as shown in FIG. 49, the N-pulse driving is performed only in the low-luminance portion. The advantage of the 匕 driving method is that it is difficult to cause the high-luminance portion due to the shortage of the current amount, by high brightness. The part does not perform the burden on the organic EL element, and the pulse is driven by the pulse, and the power is supplied to the pixel only in the whole, and the low-pitched portion of the L-ray is N-pulse driven to continuously reduce the burden on the branched EL element. The floating capacitance 451 of the source signal line is changed to a problem that a signal before the specific luminance is written inside the pixel. In the case of the low-shell portion, the lighting rate is set to 1 丨, and the total current amount is set to the target value, and the current flowing through the source signal line is increased to N2 times. At this time, it is not necessary to have N1=N2, and it is also possible to make a crime. Of course, it may also be m-N2. However, the purpose of this driver is to increase the amount of current flowing into the source signal line, so N2>: 1. Moreover, it is not necessary to lower the lighting rate, depending on the relationship between the amount of current flowing into the organic EL panel and the input data sought. It is also possible to adopt a process that does not change the lighting rate or suppress the increase of the lighting rate. Assume that the relationship between the input data and the lighting rate is as shown in Fig. 5, considering that the input data is in the 30% under-filled area, so that the lighting rate is maximized. In the region of more than 3%, the driving of the xenon lamp rate is gradually reduced in such a manner that the current flowing into the organic EL panel does not exceed the limit capacitance of the battery 241. Moreover, in the above-mentioned driving, the input data is less than 30%. N-time pulse driving is performed. That is, when the current amount corresponding to the white display is expressed by 1 〇〇, the gradation of the low current region expressed by the specific current amount of 30 or less is Nl> 1 'N2> 0 and the positive number of N1-N2 is set as a coefficient, the specific current amount is set to w, and the current value at this time is set to Iorg, and the light-emitting period is 94092-961016.doc -53 - 1295792 In the case of Torg', the amount of current satisfying the current value i〇rg χΝΙ and the period of illumination is Torgxl/N2 is applied instead of the aforementioned current amount, wherein the switching point of the n-time pulse and the normal drive is not fixed at 30%. If the life is considered, it is better to have a switching point with N times the pulse in the area below 30%. Here, two kinds of N-pulse driving methods are proposed. The first system is 5 ii, and the input data is 30%. In the full area, the lighting rate is 1/N, and the current flowing into the source signal line is N times. The second system is 5 12, and the input data is gradually reduced from 30% to 〇%. The lamp rate, on the contrary, gradually increases the amount of current flowing into the source signal line. The amount of current flowing into the organic EL panel becomes the relationship of FIG. 50, but the input data of the first method is turned on under 30% of the full condition. Both the rate and the current value are fixed, so it has the advantage of being extremely easy to make a circuit. However, at the limit of the input data of 3〇%, the lighting rate and the current value are greatly changed at the same time, so it is also at the moment of change. Flashing problem. Loss of the second method When the data is less than 30%, the lighting rate and current value must be operated at the same time, so the circuit has complicated problems. However, this method can make the lamp light rate and current value change slowly, so there is no problem such as flicker. Moreover, as shown before, the problem that the signal before the change to the specific brightness is written inside the pixel, the smaller the amount of current flowing into the source signal line, the more significant, so the current flowing into the source signal line is increased in response to the decrease of the input data. The quantity is reasonable, and the burden on the component is also reduced. By this method, a driving method is implemented, which minimizes the burden on the organic EL element, and solves the problem of writing the signal into the pixel before changing to a specific brightness. The problem. Port 94992-961016.doc -54- 1295792 FIG. 64 illustrates the circuit configuration of the present drive. The image data added by 522 is input to the reference current control module 641, and at 641, the source driver 14 is controlled in accordance with the input data 'to increase or decrease the amount of current flowing into the source signal line i8. The source driver 14 will be described with reference to FIGS. 62 and 63. As shown in Fig. 63, the source driver 14 flows a current into the source signal line 18 in accordance with the reference current 629. Further, when the reference current 629 is described, the reference current 629 is determined by the potential of the node 620 and the resistance value of the resistance element 621 in Fig. 62. Further, the potential of the node 62 可 can be changed by the voltage adjusting unit 625 and the control data signal line 628. In summary, if the control data signal line 628 is controlled by 641, it can be varied within the range determined by the resistance value of the resistance element 621. As an application example of the above-described driving method, a circuit configuration in which the above-described driving method is added to the circuit of Fig. 61 is shown in Fig. 65. The relationship between the input data and the lighting rate and the reference current value is as in the case of 5 12, and is distinguished by the region 513 in which the reference current changes and the region 514 in which the reference current does not change. When the input data is in the 513 area, the X-flag of Fig. 65 becomes 1, and when it is located in the area of 514, it becomes a structure of 〇. Further, similarly, when the lighting rate γ(1) of the frame is at 513, y_flag becomes 丄, and when it is 514, it becomes 〇. That is, y-flag becomes "the temple, which becomes the region where the reference current changes, and 651, ^^牦 is "taken, according to the information of 556, the reference data signal line 628 of the reference voltage is changed. The 65〇 is composed of a combination of y-fl牦 and X-flag. When y_flag and χ-flag are both ,, since Y is in the region, Y (t) is designed in the same program as 555. Similarly, when both 'y-flag and x-fiag are 1, the reference current changes due to the movement in the area of 513, but the calculation of the lighting rate is the same as the program of 555, 94092-961016.doc • 55- 1295792 Yes. When y-Hag and X-flag are (0, 1) or (1, 0), the state of the region of 513 is about to be moved to the region of 514 (or vice versa). In the area of 513, both the lighting rate and the reference current value change, but the multiplication always moves in a certain way. In other words, it can be said that the lighting rate of 514 is the same as the maximum condition (defined as d - μαΧ). Therefore, when y_flag is 0 and X_flag is 1, that is, when the area of 514 is moved to the area of 513, 丫 and 〇 are 11^8 again. Conversely, if 7-£1 is called 1, and X-flag is 0, that is, when the area of 5 13 is moved to the area of 5 14 , it can be regarded as D & Y toward Y gt guided by 555. (1) If it is moved, by setting the D-MAX input to the register 583 of γ(1), and designing Y > (t) in the same manner as 555, it is possible to realize a change in the lighting rate without a sudden sensation. In addition, the method of using the circuit for the curve of the lighting rate of Fig. 30 is used. This driving method can reduce the circuit scale by using the curve of the lighting rate as shown in Fig. 3 in combination. As shown in Fig. 130, the input data is divided by 2 s power, and the N-time current value and the 1/N party light rate are driven 'up to 2 n-th power input data. The value of the maximum lighting rate is a, the minimum lighting value of the usual lighting rate suppression driving is b, the value of the N times current value, the minimum lighting rate driven by the 1/N lighting rate is c, and the input data is 〇, that is, the minimum value of 2 to the nth power is regarded as CASE1 (case 丨), 2 is equal to 2 (n+ 1) power is considered as CASE2 (case 2), 2 (n+丨) The second power to the second power of S, which is the maximum value, is considered to be CASE3 (case 3). Further, FLAG_A which becomes i only at the time of CASE1 and FLAG_B which becomes 〇 at the time of CASE3 are prepared. By this, CASE1 can be (FLAG-A, FLAG a Β) == (ι, u, CASE2 can be (FLAG A, FLAG-B) = (〇, that, case3 can be (FLAG-A, FLAG- B) = (〇, 0) is indicated. Next, the circuit configuration of this driver is implemented as shown in Fig. 1. The discrimination between the values of FLAG-A and FLAG-B can be offset by The register offsets the input data and inputs it into the comparator. If the data of the offset n bits is 〇, otherwise, it is 〇, and the offset is clamped 兀 (total n + 1 bit), if 〇 FLAG-B is 1, and the other is 〇. In addition, '?1^〇一八和卩1^〇一: 6 of 0 and 1 may be reversed. Using these two curves 'made by CASE1 to satisfy 3 The right-free lamp rate is Y, the data is X (maximum 2 to the power of S), and the three equations can be expressed as follows. CASE1 ··· Y=((ac)/2n) · X + c CASE2...Y= A_2· ((a_b)/2s)· χ+2η· ((a ππ])) CASE3 ...Y=a_((a_b)/2S) · χ In order to realize the three equations, Yes, but in the circuit configuration, as the arithmetic processing system scale becomes larger, it should be reduced as much as possible. The number of row operations 'in particular, the multiplication processing imposes a large burden on the circuit scale. Therefore, the multi-purpose selector circuit and the offset register are used to realize a circuit configuration with less burden. First, ab and ac are respectively performed. This value is multiplied by the selector 13 ι. From the above equation, a_c is performed only in the case of CASE1, so ac is output when ac is eight, and a_b is output when 。 is output. The output value of the selector 1311 is calculated as the input data X. Thereby, the values of (a_b)·X and the values of (ac)·X are completed. In CASE2 and CASE3, the slope is doubled, so the output value of the selector 1311 is doubled and doubled, according to FLAG-B The value is selected in the selector 丨32丨2. At this time, as a method of doubled, there is a method of shifting the output value of the selector 丨丨3丨丨 toward the MSB side, and even if the offset register is not used. Since both are divided by 94992-961016.doc -57 - 1295792 2s, as long as the lower S bit of the output value of the selector 13 11 is cut off and the S-1 bit is cut off, the selector is multiplied. π 12 can be. The subtraction result of the output of a and selector 13 12 is consistent with the Y value of CASE3. CA SE2 is based on the result of this operation plus 2n · ((3-1))/2(^1)). Also, CASE1 can be regarded as c plus ((ac)/2n) · X ' so by this The output value and the c value are multiplied by the selector 1313 selected by FLAG_A, and then the value added to the selector 1313 is selected to obtain the lighting rate. 2n · ((a-b)/ 〗 〖1)) is to shift (0-13)/2(^1)) towards the MSB side by η bits. Further, ((a_c)/2n) · χ is (a_c) · χ, that is, the output of the selector 13 11 and the calculated value of the input data are shifted by η bits toward the lsb side. Both are offset by η bits, so the offset can be ended with one counter i 3丨4. 2n· After shifting the a_b value toward the MSB side by η bits, the lower S-1 bit is clipped and output. This two outputs are multiplied by the selector 1315. This selector is a selector for CASE1 and CASE2, so use FLAG-A. Since CASE3 does not need to add this output, FLAG is multiplied by selector 1316, and CASE3 is the output. Thereby, the lighting rate of all CASEs can be calculated by the minimum calculation and selector. Compared with the calculation by CASE1 to 3, the circuit scale of this mode is less than half, and the effect of realizing this configuration is extremely high. In general, images use a gamma curve. The so-called gamma curve is obtained by suppressing the low gradation portion so that the entire image is processed with contrast. However, if the low gradation portion is suppressed by the gamma curve, the image having a large number of gradation portions will be black and collapsed, and an image having no sense of depth will be obtained. However, if the gamma curve is not used, the image with more high gradation will not appear as the opposite image. " 94992-961016.doc -58- 1295792 In the case of performing the lighting rate control driving of the present invention, if the display area has a low gradation display, the lighting rate is increased to make the whole light. At this time, if the low gradation portion is broken by the gamma curve, since the luminance difference between the displayed pixel and the undisplayed pixel becomes large, it is possible to become an image having no depth. Further, when the display area has a high gradation display, the luminance difference between the display pixel and the non-display pixel is reduced because the lighting ratio is lowered. Therefore, if the image is not broken by the gamma curve, it will become an image with no contrast. Therefore, it is proposed to control the driving method of the gamma curve by the change of the display area in conjunction with the current amount control drive of the present invention. The circuit configuration for realizing the r-curve will be described with reference to Figs. The input color data is taken as the horizontal axis of the curve and divided by 2 η power. In Figure 67, there are 8 divisions, which are 671a, 67 lb...671f. Further, values 672a to f of the r-curve corresponding to the boundary of 67 ia to f are input. In Fig. 68, it is assumed that the input color data is 8-bit. Initially, the upper 3 bits of the input data 680 are determined at 681. Since the gamma curve (the third power of 2) is divided into eight, the value of the upper three bits of 680 can be used to determine which region of the input data 680 is located in 67la~f. Assume 680 is located in the area of 671c. The gamma curve of the 671c has a minimum value of 672b and a maximum of 672c. Since the input data of the 256th stage is divided into 8 divisions, the 1 interval is divided into 3 2 stages. Therefore, the slope of the curve of 6 71 c is (672b_672c)/32. Since the region of the input data located in the region of 671c is equal to the value of the lower 5 bits of 680, the value of (lower 5 bits) 672 (672b-672c) is shifted by 5 bits toward the LSB side ( Divided by 32), and become an increase in 671c. That is, the value of 672b is added to the above, and the output value 682 of the input data 680 is converted by the gamma curve. 94992-961016.doc -59- 1295792 Next, a circuit configuration 557 for indicating the display state of the organic EL panel and the like, which is performed in 552, and a circuit configuration for adjusting the gamma curve in accordance with the display state will be described with reference to Figs. First, at 691, the values of 661 & Here, 661-662 was established. Since the 7 curve varies depending on the device used, this value should be set externally. Further, the differences 663a to f of 661a to f and 662a to f are obtained. Thereafter, 691 a to f and 663a to f are outputted by 691 for 692. At 692, the data 557 of the display state outputted by 552 is also input. At 692, the value of the 7 curve is determined in accordance with 557. The larger the 557 is, the more the gray level of the image is. The gamma curve must be tightened, and the image is added with strong and weak. The smaller the 557 is, the more the low gray level part of the image is. The gamma curve must be relaxed to make the image with depth. . Since 557 is a data of 0 to 255, the gamma data according to 557 is made by the operation of (661 &~£)-{(663&~£) parent (557 data/255)} 693a~f. The gamma data 693a~f is input to 683. The 683 is as illustrated in Fig. 68, which outputs the color data 680 input by the gamma curve converted from the data of 672a~f. group. Inputs 693a to f at 672a to f, and 5 of the input RGB data are converted by the gamma curve made by 693a to f, and input to the source driver 14 as the output 696. In the above description, the data corresponding to the 557 is subtracted from the gentle gamma curve 661, but it is of course possible to add the data corresponding to the 557 by the condensed gamma curve 662. Further, the gamma curve is not limited to being made of two types. A structure in which a gamma curve of an image is displayed by a complex gamma curve can also be used. The change in the gamma curve is also the same as the change in the lighting rate. If there is a frequent change of 94992-961016.doc • 60-1295792, it will appear to be flickering. Therefore, as with the delay of the change in the illumination rate by 612, 557 also delays the rate of change very effectively by 612. In the figure, RGB is processed in the same manner as 694, but by RGB, it is also possible to make RGB individual gamma curves. In the case where the above-mentioned driving is used in the case where there are many low-gradation portions in the display region, by using the gentle gamma curve to present the sense of depth and the high gradation portion, the gamma curve can be tightened, and the contrast can be presented. drive. In addition, as a means of making RGB independent gamma curve, gamma curve 672 made as shown in i29, plus correction value 1291 a~1291 f ' in rgb, respectively, can be used to make gamma separately. curve. In this way, the operation of the complex gamma curve is completed in one type, so that it can be realized without increasing the circuit scale. Since the organic EL element 15 is deteriorated, if only the fixed pattern is displayed, only the organic EL element 15 of a part of the pixels deteriorates. The displayed pattern may leave a residual image. In order to prevent image sticking, it is necessary to discriminate whether the image is a still image. As a method of discriminating a still image, first, there is an internal _ _, and the data of the period of the period is all stored in the frame memory, so as to determine whether or not the image data of the sub-frame is positive or not, and whether or not it is a still image. This method has a clear understanding of the different advantages of image data, but the eight-gate A frame memory, so the circuit scale becomes enormous. It is judged by the frame memory that there is an increase in the 1F period. Image when the image is unchanged. Therefore, the addition of 1F is therefore proposed as a method of not making a still image as shown in FIG. The method of judging the total value of the data of the full pixel as the judgment method is also unchanged, so the total amount of the data is unchanged. 94992-961 〇 16.doc -61- 1295792 All the data are compared and can be detected as a still image. If this method is used, it can be realized with a very small circuit scale as compared with all the image data. However, in a specific pattern, the method of obtaining the total amount of data has a situation in which the effect cannot be exerted. For example, when there is a white block flying in the black box, even if the position of the white block is different, the total amount of the data is the same, so the still image is mistaken. Accordingly, the present invention proposes a method of making data by combining a plurality of pixels so as to have a correlation with data of other pixels. First, the '711 is operated by data enable (DE) and clock. This is because the information is not always coming, and only the judgement is made for the necessary information. As shown in FIG. 70, when inputting 6-bit image data 7〇la, 7〇lb, an 8-bit register 7〇2 is prepared, and the upper 4 bits of the respective image data are input to the odd and even bits. , constitute a register. At this time, the register 7〇2 does not need to be 8 bits το, although the circuit scale becomes larger, but it can also have a 12-bit scratchpad. If the accuracy of the party can be reduced, the temporary storage of less than 8 bits The composition of the device is also possible. In addition, the proportion of the two video materials was changed. When inputting an 8-bit scratchpad, it can also be 5 bits from 7〇la and 3 bits from 7〇lb. Moreover, the data input to the scratchpad does not have to be obtained from the upper position, and the lower 4-bit input may be selected. It is also an effective means to change the acquisition location according to the value of the counter 713. As shown in Fig. 70, when viewed in 2 pixels, the case of 7〇3 is the same for any one of the patterns, but in the case of 704, the data becomes different, so that the still image is not mistaken. Since FIGS. 70 and 71 simplify the description of the driving method, there is a correlation between the two pixels, but it is also possible to have three or more pixels. If the method of FIG. 70 is performed in a plurality of pixels, the advantage of the detection accuracy of the still image is improved 94492-961016.doc -62 - 1295792, but the number of bits of the register 702 becomes large, so that the circuit scale becomes large. Disadvantages. Therefore, as shown in Fig. 74, a method of maintaining a correlation between a plurality of types of registers different in the number of bits is prepared. The value of the logical difference is calculated by adding the data of the register and the value of the counter 713 to the 712 system. The counter 713 is reset by a horizontal synchronizing signal (HD), and is a module with a positive number by a clock. Therefore, the weight of the horizontal direction coordinate can be added to the data by logically calculating the counter and the data, as in the horizontal direction coordinate indicating the display area. At 714, the value of the data of the 1 level period and the value of the counter 715 are added to perform the value of the logic operation. Counter 715 is reset by a vertical sync signal (vd), a module that is positive by HD. Therefore, it is the same as the coordinate indicating the vertical direction of the display area. By logically calculating the counter and data, the weight of the vertical direction coordinates can be added to the data. By using the above method, the accuracy of still image detection can be improved. However, it is not necessary to use all of the above methods, and the above method is a method for further improving the accuracy. It is not impossible to detect a still image without using all the above methods. By combining the forms of the above methods, the information of the 716 716 716 « Front 贞 贞 717 and 718 are formed for comparison. As a comparison method at 718, the two data do not necessarily need to be the same, and the image data may be exchanged for noise. Therefore, as long as there is no data without noise, the two data will not be the same. At 718', the error range of the two data can be determined according to the necessary accuracy. As a comparison method, in addition to the method of subtracting two data and judging whether it is a still image by the calculation result, the data m of the previous frame is inverted at the beginning of the frame, and is input to _ (storage m6, according to Addition between 1F (4) 94992-961016.doc -63- 1295792 Material 716 is close to G, riding adder, _ by board ^ ΓΓ 712, 714 ^ 〇 degree to determine whether it is a still image method 1 subtraction In the vicinity of the figure: Figure I!, by adding all the data in the display area to determine whether it is a different image of the still image view, there may be a case where 5〇% is the number of still pictures 5|7H5iU is an animation. Therefore, It is also effective by the counter 713 and the method of dividing the face into plural numbers to determine whether or not a certain range in the face is a still image. Γ 1 8 when it is determined as a still image, When the counter 719 is positive, the counter 719 is reset. In short, the value of the counter 719 is a period during which the still image continues. A method of reducing the speed of light and reducing the lighting rate. When the number of people 719 becomes a certain value, the operation signal line 71〇1, when the signal, , and 1 are in the ΗΙ, forcibly control the signal line of the lighting rate. In 710, the connection brightness control value 556 is prepared and The module of the signal line 71〇1, when the signal line 71〇1 is HI, forcibly reduces the lighting rate to the current 1/2 to form a circuit. At this time, the value of the forced reduction of the lighting rate does not need to be fixed at 1/2. In order to reduce the lighting rate, the organic EL element 15 reduces the amount of light emitted, which may slow down the rate of deterioration of the life. Of course, 71〇1 is: when the boundary is used, the lighting rate is lowered. It is also possible to control the mode. However, even if the deterioration rate is lowered by the above method, if it flows in a long time, it will cause image sticking. Therefore, when the still image continues for a long time, the current flowing into the organic EL element 15 must be completely stopped. Therefore, the signal line 62b is forcibly operated by the signal line 94092-961016.doc -64-1295792 7102 to forcibly turn off the switching element during which the control current flows into the organic element, preventing current from flowing into the organic EL element. The signal line 62b is as previously indicated , its system The operation switching element is called the line ^7, forcibly fixed to the signal line of either of HI and L〇w, and by controlling the signal line 7102, the still image can be continued for a long time. Since the organic EL element emits light, the image sticking of the organic EL element can be prevented. Further, in the display device using the organic EL element, it is advantageous to detect the still image system. As described above, the organic EL element can be intermittently driven. The invention also controls the lighting rate control value to control the lighting rate. In the first place, by inserting black once in an intermittent manner, the image wheel gallery can be made clear and the image becomes very good. However, the insertion of black at one time has the disadvantage that the black area to be inserted becomes larger, the human eye can catch up with the black insertion, and the black insertion will appear to be flickering. This is mainly a problem common to still images. In the case of animation, the black insertion flicker is not visible due to the change of the image. Inserting black will improve this phenomenon, but you cannot use the effect of inserting black at the same time to make the outline clear. Therefore, there is proposed a driving method for preventing the flickering of a still image by inserting a black sub-segment when the static display is detected as shown in Fig. 72. A circuit configuration for inserting black in order to use the counter 554 and the lighting rate control value will be described with reference to FIG. As previously indicated, the switching transistor 丨id is controlled by the gate signal line 17b, and the gate signal line 17b is determined by the ST2 input to the gate driver 12. As shown in Fig. 75, if ST2 is repeatedly turned on/off in m units, the switching transistor ud will be turned on/off repeatedly for each 111, and 94992-961016.doc -65·1295792 becomes an image inserted as 722, which is divided into black. Therefore, most of the use of a selector such as 73 i implements black split insertion. 71 电路 Circuit configuration First, first pay attention to the LSB of the counter 554. The selector 73 1 outputs the value of B when the input value S is 1, and outputs the value of a when 〇. That is, if the value of the LSB of the counter 554 is 1 in consideration of 73 la, the value of the MSB of the lighting rate control value is output. When lsb of counter 554 is 〇, it reflects the output value of 73 ib. 73 lb is in the case where the second bit is 1 from the low position of the counter 554, and the lighting rate control value is 8 bits, and the value of the seventh bit is output, and the third bit and the fourth bit are repeated... The circuit is constructed. The LSB of the counter 554 φ is HI and LOW repeated every 1H. When the lighting rate control value is 8 bits, since the eighth bit is 1 or more, it is 128 or more. Therefore, it is necessary to have HI once every 211. That is, when the LSB of the counter 554 is set as the selector switch, when the value of the MSB of the case light rate control value is output when lsb is 1, the ST2 becomes HI once every 2H. When LSB is 〇, the signal value from the selector to the left of HSI is output to ST2. Moreover, the counter 554 is 〇, and when the first bit 疋 of the lower bit of the counter is 1, the seventh bit of the lighting rate control value is output. In the end, the seventh bit of the rate control value is output once every 4H. If the same _ continues, it will become the sixth digit of the lighting rate control value, which is the type of complaint that is output every 8H. By combining this, it is possible to convert from black one insertion to black division insertion. By constructing the circuit in which the black partition is inserted, and in the circuit method group for detecting the still picture including the method of the duck memory shown previously, the black insertion is performed once, so that the contour is clear. The driving method is a static drawing, and by inserting the black segmentation, the driving of the flicker caused by the insertion of a 94992-961016.doc -66 - 1295792 can be realized. As a means for pulling out the floating capacitance 451 of the source signal line 8 shown in the first 4, there is a method of preparing a voltage source 773 having a low impedance and applying a voltage to the source signal line 18. The above method is called pre-charge driving. Fig. 77 shows the circuit configuration of the precharge drive. A voltage source 773 and a voltage applying means 775 are provided in the circuit. When the voltage application means 775 turns on the switch, the voltage source 773 charges and discharges the floating capacitance 451 of the source signal line 18. For ease of illustration, the 774 is depicted separately from the source driver 14, but the 774 can also be built into the source driver 14. When the circuit configuration of the source signal line 18 which can be precharged by the voltage application means 775' is selected, the pre-charging can be turned on/off in units of pixels, so that fine setting can be performed. The present invention is based on the above-described circuit configuration using the still image detecting means 711, and a frame memory or the like may be used instead of 711. Compared to animation, the image degradation caused by the floating capacitance 451 as previously shown is more pronounced. Therefore, by detecting the still image by 711 and pre-charging by operating the voltage applying means 775' by the comparator 772, it is possible to prevent image deterioration at the time of still image. As described above, in the case of displaying the moving cymbal, in order to make the outline clear, it is preferable to insert it once, but in addition, it is preferable to drive the electric surface of the gate driver circuit of the organic EL display device, and it is preferable to insert black at a time. . Further, the gate driver 12 for driving the EL display panel operates the gate line 17b by the shift register 61b which operates the start pulse ST2 by the clock CLK2. As shown in Fig. 78, when black is inserted once, each gate signal line 17 can be turned on and off once during one frame period. However, as in the case where 782, 94992-961016.doc -67 - 1295792 is inserted in black, the gate signal line 17 is repeatedly turned on and off. Therefore, turning on and off the complex signal lines at the same time has a problem that the power consumption of the gate driver 12 becomes large. From the above point of view, it is generally preferred that the organic EL display device insert black at a time, however, in the case where black is inserted once, the flicker caused by the insertion of black once is observed in the still image. Therefore, the explanatory diagram of the display state of the panel in which the present invention is mounted displays a still image or an image with little motion. In the case of displaying a still image or an image with few motions, it is necessary to have a black insertion change into a split insertion once, but if it is changed from one insertion black to a division insertion, it appears to blink at the switching instant. There are two reasons for this. The first reason may be that the luminance is degraded when switching to one of the split insertions, as shown in Fig. 79, it is considered that the s horizontal scanning lines are lit in the p horizontal scanning lines. At this time, the number of scanning lines that are not lit, that is, black is p-s (bar), and when the two are divided, the number of scanning lines that are not lit is (p_s)/2 (bar). The scanning line of the current sever is turned on before switching, but only at the moment of switching, between s/2 (strip) redundancy and (PS)/2 (strip), the number of scanning lines becomes §/2 . During this period, since the luminance of the display area is s/2, although the luminance is reduced in only one frame, it may become image degradation. The second reason may be that the black interval changes rapidly. If black is inserted at one time, as one of the causes of image deterioration, it may be that the human eye unconsciously catches up with the insertion of black. Therefore, when the black segmentation is inserted by the state of black insertion, the interval at which the image is rapidly changed is felt, and the image is deteriorated. The present invention proposes to solve the above two problems, and there is no image degradation. 94992-961016.doc -68-1295792 The black insertion method is changed from one insertion to a divisional insertion method. The image degradation caused by the switching is caused by the rapid change in brightness and black feeling as described above. Therefore, as shown in FIG. 89, the present invention prevents the switching when the black interval is gradually divided between the plurality of frames. Like deterioration. Fig. 8 is a diagram showing the change in luminance when the horizontal scanning line number is divided by two during the N horizontal scanning period (indicated by h after the horizontal scanning period). In the case where the s horizontal line is illuminated, if the start pulse of the two divisions is 801 and the latter is 802, the number of light horizontal scanning lines of 8 () 1 and 8 () 2 becomes (S 2 4, 6...). Therefore, the start pulse of the previous stage is output to the gate _ I line and after the S/2W period, the number of horizontal scanning lines p of the EL display panel is (S/2)-N" The brightness is as follows before switching: { (p/S } Xl00(%)...(6) The curve shown in Fig. 81 is shown by a curve in Fig. 79 and the figure, and the redundancy is used once at the time of the knife edge. Brightness is closely related to image degradation. The value of 弋() is p SN, so as shown in the figure, the change is due to 8 and ^. According to the measured value, if the value of the analytical formula (6) is less than 75%, the image will be caused. Therefore, the value of the proposed formula (4) is more than 75% of the value of the formula (4), that is, according to the formula (6), N^s/4 (where Nd), the black insertion gap is increased. If the value of the formula (6) is 75% or more, the image deterioration will not cause the image to be more than 8〇%, and the effect can be expected. It is preferable to be (eight)% or more S/10). However, in the present invention, if the brightness is less than 75%, it is possible to change. In Fig. 79' s horizontal scanning line lights up (4) when the number of lighting horizontal scanning lines is divided into 2, divided into s/2, but this is divided into 8, strips and s_s> strips are not 94092-961016. Doc -69- 1295792 :(two <S). Further, the amount of the -sub-division is not limited to the two-division, and it is assumed that N=3, and the right second is 90% or more per one horizontal scanning period, and even if the four-division is still held once, the processing does not affect the processing. Fig. 82, the insertion and the insertion interval are 疋' so that the control light interval is moved to the next minute f until the black insertion interval is the same. However, as shown in Fig. 83, the knife can be adjusted first. Insertion interval. &, lighting interval: The effect of improving the image degradation is high, but it does not necessarily need to be consistent. The method is to gradually increase the black insertion interval, but it can also use the reverse to gradually reduce the xenon lamp level. The method of scanning the number of lines. If the condition of W lighting is divided into W and N, and then the method is divided into S rhyme and 2N method, the brightness will not become less than %, so it will not lead to Deterioration of the image caused by the gradation. This method should be caused by a sharp change in the black insertion interval of the first cause of the image 7, and thus image degradation occurs. However, as described above, the image degradation caused by the change in luminance may be Solved, so effective Fig. 85 shows a circuit configuration diagram for realizing the driving method of the present invention. The circuit configuration of the present invention comprises: two counter circuits 851, 852; and an added value control circuit 855 for controlling a circuit for generating signals by the two counters. 853, (10) and the added value of the two counters; and the selector (4) outputs any one of the output 856 outputted by (5) and the output 857 outputted by 854. The circuit 854 is illuminated by the light shown in FIG. The circuit that divides the value of the control value and the value of the counter w and outputs the waveform is reconstructed into a circuit with less delay. The circuit of Fig. 73 is the same as the 854, and any circuit can be used. The circuit 853 is when the counter 851 is 0, The output 856 becomes HI. Moreover, in the added value control 94092-961016.doc -70-1295792 circuit 855, the output lamp 856 is generated by the shell lamp rate control value. The ten value. The TO lamp rate control value is N bits. When the start pulse ST2 of the input gate driver 12 is divided into two t-th powers, the output 856 becomes L〇w at the time of the value of the high-order (Nt) bit of the lighting rate control value. 851 is set to (Nt) bits When the value becomes !, it is initialized to 〇. When this counter 851 is initialized, the selector 858 is controlled to select the output 857 from the circuit 854. The setting as described above is performed to facilitate the formation of the circuit. The π lamp rate control value is not required. For the divisible value, when the start pulse is divided into two t-human sides, when the shell lamp rate control value cannot be divisible, the start pulse after the division becomes a different length. The start pulse with different control lengths requires a new constituent circuit 'circuit configuration Therefore, it is advantageous to use the circuit configuration as described above. When the start pulse is divided into 2 to the power of t, the value between the t bits is divided by the low bit of the lighting rate control value to divide the lighting rate control value. By dividing the remainder of the t-th power of 2, the circuit division can be performed by complementing the remaining portion. When the circuit ' shown in Fig. 73 equivalent to the circuit 854 changes in the south bit t of the counter 205, the data output between the t bits is started in accordance with the lower bit of the lighting rate control value. The high position of the counter 852 is synchronized with the initialization of the counter 85 1 when changing between the epochs. Therefore, by the selection 858 selecting the output 857 of the circuit 854 at the initialization of the counter 851, the remaining portion can be complemented by The start pulse can be divided completely. Using this circuit constitutes a reduction in circuit scale. Using the actual values, the processing flow of the above circuit will be described with reference to FIG. 861 is the output 856 of circuit 853, 8 64 is the output 857 of circuit 854, 8 63 is the value of counter 94992-961016.doc -71 - 1295792 851, and 864 is the value of counter 852. The lighting rate control value has a value of 3 in the valley of 3 bits, and 011 in the case of 2 digits. When this is divided into two, it becomes t=i. Therefore, the value of the initial value of the counter 851 is set to 11, which is 3, which is 3, and the output of the circuit 853 is lowered to L〇w. Qi, 10 is 1. In circuit 853, the counter 851 is 〇, the output becomes 扪, and if the output is LOW, the output is LOW. In circuit 854, when counter 852 is 2, 4, 6, the output is HI. The period of the selection output 857 of the circuit 854 is when the counter 851 is initialized, that is, when the counter 8 5 2 is 4, if the two outputs are synthesized by the above circuit configuration, it will become like 865, and it can be confirmed that the start pulse can be obtained. 2 split. Next, a circuit configuration relating to the insertion interval of the gradually varying black using the added value control means will be described. The added value control means 85 5 is used to simultaneously control the two counters 85 852. The added value control means 855 distinguishes between the state of each added state, the added lighting rate control value, the number of waveform divisions or the value derived from the interval of black insertion, and the state of not adding any state, depending on the situation. In order to control the black insertion interval. The state change of the added value control means will be described with reference to FIG. The value initialized by the counter 851 is set to γ, and the value of the output 856 to LOW is set to X. 8701 is a vertical sync signal, 87〇2 is the start pulse of the black one-insert state, 8703 is the state of the black insertion interval 8704 of the previous stage as the state of N(H), and 8705 is the interval 8704 of the black insertion of the previous stage and the latter stage. The interval of the black insertion 8706 is substantially in the same interval state. If the state of the 8703 is changed to the state of 8705, the above image degradation is caused. Therefore, in the state of 8703, the black insertion interval 87〇4 of the previous stage is gradually increased to N, 2N, 3N, ..., and finally becomes the state of 8705. To prevent image degradation of 94092-961016.doc -72-1295792. The operation of the add value control circuit 855 regarding the state of 8703 will be described based on the graph of Fig. 87. The dotted line shown at 8707 is a curve of the value of the counter in the case where the counters 851 and 852 are each falsely rising. With respect to this, the curve 8708 of the realization is a graph of the value of the counter which controls the increment of the counters 851, 852 by the added value control circuit 855. The added value control circuit 855 is controlled by one increment counter 85, 852 so that the value of the counter 851 becomes X. Moreover, the counter 851 is at the time point again, and the start pulse becomes LOW. Originally, the next start pulse is the Y when the counter 851 is initialized, and there is a period of γ_χ(Η) therebetween. Here, the added value control means 855 is controlled to add a value as indicated by 8709 until the counters 851, 852 become the value of Υ-Ν. Thereby, the time until the start pulse is next changed is shortened to Ν (Η). Here, the added value control means 855 is, for example, 8710, and adds the value to the counter 851, and returns the value to 1. The counters 851, 852 are after N-1 (H) and have a value of γ. The period until the γ value is changed by the addition method of the value of 87〇9. When the value of 8709 is asynchronously added to the counter 851, the period until the Y value is reached may become N(H). In the present invention, any addition can be made. Therefore, the counter 851 is initialized, and after the output 857 is selected, the start pulse is again HI. Thereby, the interval 8704 of black insertion in the front stage becomes N (H). After the start pulse becomes m, after χ(Η), the start pulse becomes L0W again. Here, as shown in 8711, the added value control means 855 controls the counters 851 and 852 so that the counters 851 and 852 are not added, in order to make the values of the counters 851 and 852 equal to the values. The counters 851, 852 and 87G7 have the same value by the same period of time as the value added during the period of 8709. If the values of the counters 851 and (1) are the same as 94992-961016.doc -73 - 1295792 8707, the added value control means 855 returns the values of the counters 851, 852 to 1. Fig. 88 shows a change diagram of the counter 851 ' 852 when the division is changed from 2 divisions to 4 divisions, and Fig. 89 shows the change in the interval of the black insertion at that time. According to FIG. 89, it can be understood that, by using the above-described driving method, a driving method for gradually adjusting the black insertion interval can be realized, which is an image which is caused by image degradation caused by rapid brightness change and rapid black insertion interval variation. The problem of deterioration. "This fx month system /, to charge the electric charge programmed by the storage capacitor 丨 9, the switching transistor Iid turns on and off the current flowing through the driving transistor 1 & or 2711?, so that the control current is applied to the organic EL element 15 The circuit configuration during the period is not limited to that shown in Fig. 1 'as in the circuit configuration of Fig. 27. Further, the TFT used for the circuit configuration is a p-channel or an N-channel, and does not affect the driving method of the present invention. The circuit configuration shown is an N-channel configuration, but the configuration is also applicable to this configuration. Further, the configuration of the source driver 14 is not affected. Even if the storage capacitor 9〇1 is charged with a direct voltage as shown in Fig. 90, the driving is performed. The voltage driving circuit driven by the crystal 9 〇 2 can also use the driving method of the present invention, and can also be used for the display which determines the current amount by using the mirror ratio of the TFT which is generally called a current mirror as shown in Fig. 76. The method is to control the lighting rate, and the driving method of the current value of the control panel 'but as shown in FIG. 96' can also be adopted to control the lighting rate by inputting the signal line ST2 of the input gate driver 12 into the 961 mode. Group, such as 97 shows a method of controlling the amount of electrons of the source driving H 14 to adjust the current of the source signal (4) and controlling the amount of current of the panel in such a manner as to be a current value according to the lighting rate. The invention records as 94919-961016.doc -74- 1295792

As shown in Figure 98 above,

When the temperature of the device rises, the amount of current flowing into the device can be suppressed, so that the life of the organic EL element can be prevented from being improved. As shown in FIG. 12, the organic EL element is proportional to the current flowing into the organic EL element 15 and the amount of light emission is increased, and the current flowing into the organic EL element can be expanded by the display of the organic EL element by & The range of performance of the image. However, as described above, the apparatus using the organic EL element is proportional to the amount of current flowing into the device, and the temperature rises, so that the organic EL element is deteriorated. Accordingly, the present invention has been proposed to extend the driving range of the shirt image by controlling the lighting rate from the display data to control the amount of current flowing into the device. However, this driving method also has a limit on the control of the lighting rate, so that the expression range of the image cannot be extended to the magnification of the lighting rate. Therefore, as shown in FIG. 92, the present invention proposes a reference for controlling the current flowing into the source signal line by controlling not only the lighting rate but also the amount of electrons of the source driver 14 when the input external data is small. The current value increases the amount of current flowing into the pixel, and expands the driving method of the image representation range of the display using the organic EL element. Fig. 93 is a view showing the external data at the time of driving and the current amount of the entire device. 93 1 About the current when the drive is not used 94992-961016.doc -75- 1295792 The value '932 is the current value when the driving rate of the present invention is used to suppress the driving. And the current value obtained when controlling the amount of electrons is 933. As in this figure, if the value of the varying electron amount is set to P, the value of the external data which is driven to the maximum current value by the lighting rate control is set to P, then the external dataχ Become an OSxSp. Figure 94 shows each! A plot of the grayscale and brightness of a pixel. 941 is a diagram when the lighting rate control is not driven. 942 is a relationship diagram of the maximum lighting rate in the case where the lighting rate has been performed. In addition to the lighting rate control drive, the 943 is also a diagram for controlling the reference current control drive. In the relationship between the life and the battery, if the current flows only in the relationship of 941, it flows. The ratio of the maximum and minimum lighting rate is 3: 丨, if the lighting rate control is driven, the 942 can be illuminated at 4 times the brightness of 941. In addition, and in the case where the reference current value is changed to 3 times in the electrons of the source driver 14, the 943 can be illuminated at a brightness of 942 times, if compared with the 941, With 12 times of redundancy, the performance range per pixel is 12 times, which enables colorful image representation. In order to increase the amount of current flowing into the organic EL element 15, the amount of current of the source driver 14 is controlled as described above. The control method is not limited to the amount of electrons. For example, the D/A comparator can also be used to vary the voltage. When the storage capacitor 19 is directly charged by voltage, the present invention can be applied as long as it can control the charging voltage by digital data. The setting in the electronic system utilizes the output of the display data totaling circuit 95 1 . In Fig. 95, the data is displayed as RGB as the image data. However, any data that can confirm the condition of the device using the data of the thermistor can be used. 95 i has the same construction as 552 in construction. The difference with 552 is that the output 94992-961016.doc -76-1295792 is more than the number of bits required to control the lighting rate. Assume that the 952 is designed to output the high-order octave of the total value of the image data when the number of bits required to control the lighting rate is 8 bits. This bit is divided into 8 bits to control the lighting rate. At that time, the remaining low 2 = can be regarded as the decimal point of the upper 8 bits. The electron driver of the source driver 14 is 6 bits in the summer, and the lighting rate is 1 〇. When the amount of electrons is controlled in the area not full, the 951 controls the amount of electrons in order to control the octet required for the lighting rate control. , plus 6 bit points, the output totals 14 bits. This is the output of the ^ 951 output is more than 15 bits, of which the high-end shirt is used for the lighting rate: the low-level 6-bit is used for the control of the electronic quantity. Moreover, it is also possible to use the bit which is used to control the party lamp rate and the bit used to control the amount of electrons to overlap. For example: 951 for 10-bit output 'High 8-bit for control of lighting rate, low 6-bit for controlling electronic quantity, low-level 4 bits of lighting rate control data and high level of electronic control 4 The bits use the same bit. Both the lighting rate control and the electronic quantity control control the amount of illumination of the device, but the direction of the brightness (making the variable or darkening) is the same, so there is no problem in the image. In summary, in the state where the lamp-free rate control requires a bit 'electronic quantity control to require W bit, when 951 outputs X bit, the high bit a of the 951 output is used for the lighting rate control 'low position. The b bit is used for electronic quantity control. The round-out data of 951 is caused by the reversal of the electronic circuit and the display data due to the change in the amount of electrons and the fact that the value of the electrons becomes larger. As shown in Fig. 92, if the display data is smaller and the driving rate of the lighting rate is increased, the structure of the electronic quantity is increased as the data is smaller. Therefore, by using the NOT circuit to invert the data, the Η_τ circuit can be realized, and the smaller the data is realized. 94992-961016.doc -77- 1295792 The structure in which the electronic cymbal becomes larger. Thereby, it can be realized without increasing the circuit scale. /匕Comparative circuit 954 is an output enable signal for the block controlling the amount of material. In comparison, the data outputted by the Road 954 system 951 is N bits, and the low bit unit is used in the electronic; if S* determines whether the bit (N_n) bit is 〇, the enable signal is output. Thereby, it is possible to realize a circuit configuration in which the amount of electrons is controlled by a specific display material without increasing the circuit scale. Also, as shown in Fig. 99, the low-order bit of the value of the control lighting rate is used. The principle of operation is the same as described above, but when the value of the lighting rate is controlled, the lighting rate is larger, and the value of the electron amount is larger, so that it is not necessary to add a NOT circuit. As shown in Fig. 61, this mode is effective when the display data is used to control the lighting rate, and when the module for preventing the delay of the flashing is used, it can be used simultaneously with the delay processing. Whether or not the NOT circuit is required, the configuration of the amount of electrons in the source driver 14 also changes. The switch of the electronic quantity changes in HI or changes in the 〇 〇 hip, whether the circuit needs to change etc. In this way, the signal line is used to control the lighting rate, and the electronic cymbal is controlled, so that the circuit scale is almost constant and the amount of control electrons can be realized. Moreover, by this processing, the performance range of each pixel can be increased, so that more color image display can be realized. The deterioration of the organic EL element depends on the temperature of the device, and the rise in temperature of the device depends on the sum of the current amount flowing into the device and the portion of the current flowing into the device. Therefore, in order to prevent deterioration of the organic EL element, a configuration in which the amount of current is operated in accordance with the device temperature is required. As a method of sensing the temperature of the device, there is a method in which a thermistor is disposed in the device, which is converted into a digital data by a thermistor and an A/D converter 94992-961016.doc • 78 - 1295792. However, this method requires the thermistor to be disposed inside the device or inside the pixel, and the A/D converter is also required for sensing as digital data, and thus has a problem that the circuit scale becomes large. Therefore, the present invention proposes a method for controlling the temperature of the scanning line by using the image data previously shown in FIG. 111 to control the temperature. The driving method 0 for controlling the temperature is shown in FIG. The relationship between the image data and the number of lighting horizontal scanning lines when the driving method of the number of scanning lines is turned on. Since the relationship between the number of lighting horizontal scanning lines and the current flowing into the device is 1010, the amount of current flowing into the device can be grasped by performing arithmetic processing from the scanning level of the lighting level and the image data. Therefore, the circuit shown in Fig. 102 is used. 1020 is the image data displayed on the device. 1〇21 is a circuit for processing the input image data. Assuming that three colors of RGB are input and rgb has a difference in the amount of current flowing into the device, a more accurate current value can be calculated by adding a weight to the data within 1〇21. In addition, in the case where the data accuracy is not high, by cutting the low-order bit at 1021, the data accuracy is reduced, but the amount of data itself is reduced, so that the circuit scale can be reduced. 1〇22 is a circuit that adds data from 1〇21. Normal image data is displayed between 5〇1 and (10)Hz, so the image data changes at the same speed. However, as previously shown, in order to prevent deterioration of the image, the change in the number of scanning lines of the light gradually changes over the number t贞, and it can be said that the image hardly grows large in the raft. Therefore, the average current value of the number (4) is obtained by dividing the data by the arithmetic number. At this time, the sum of (4) should be 2 to the nth power. Addition (4) is not the ♦ power, in order to get the right level 94992-961016.doc -79- 1295792 Mean' must use a divider, the circuit scale becomes larger. When the number of added frames is η power of 2', by shifting the added value toward the LSB side by η bits, the same effect as the division is obtained, and the circuit scale is reduced. As described earlier, since the change in the number of horizontal scanning lines of the light has passed through 1 to 2 frames, the output of 1 to 22 should also be averaged from 16 to 256 frames. In the case of 6〇 影像 image data, 1 second has passed 60 frames 贞' Therefore, if the average value of 64 frames is specifically obtained, the output data of 1〇22 can be regarded as the average current per 1 second, so it is easy to grasp the current amount. The output of 1022 is a circuit 1024 that contains a current value for a certain period of time including FIF(R) memory 1〇23. The FIFO memory 1023 is a built-in memory for controlling the write address and the counter to read the address. Since the latest data and the oldest data in the memory can be simultaneously seen, the memory can be frequently used by using the Fif memory. Master the current data for a certain period of time. Furthermore, in this case, the memory does not have to be a FIFO. By controlling and controlling the counters of the prepared address in order to write and read, the control of the new data and the old data is the same as the use of the FIFO. The configuration of the circuit 1024 for grasping the current value for a certain period of time using the FIF0 memory will be described with reference to FIG. As previously shown, the FIFO memory system has built-in memory that controls the write of the address and the counter that reads the address. The FIFO memory issues a FULL signal 1030 when the write address comes to one of the read-in addresses. This indicates that the write address comes before the read position, in other words, the output data 1032 from the FIFO in the state in which the FULL signal 1030 is issued is the oldest data in the FIFO memory. 1033 is a register for storing the total added value of the internal data of ]pIF. Since the FIFO is a structure for replacing data, the difference between the output side data 1032 and the input side data 1034 is obtained, and is added at 1035. The 1036 selects the selector from the FIFO by means of the FULL signal 1032 94992-961016.doc -80 - 1295792 or 〇. When the FULL signal appears, select the output from the FIFO. When it does not appear, select 0 to enter the difference between the latest data and the oldest data in the FIFO memory. Moreover, by adopting this method, it is possible to ensure the accuracy of the circuit from the time of starting up to the time when the FIFO δ memory is full. The fif〇 memory system has a write enable signal 1031 and a read enable signal 1〇37. When the enable signal is input, the input data is written in the write address by the input block of the FIFO memory, or read in. The output data is 1〇33. The write enable signal is controlled by a circuit of 1〇38, and the enable data is read by the full signal. The read enable signal is input to FIF0 only when a full signal occurs, and the write enable signal is not input to FIF0 when a FULL signal occurs. By using such a circuit, the accuracy of the internal data of the FIFO memory can be improved. Due to the capacity of the FIFO memory, the data that can be stored, that is, the amount of current, varies during the measurement period. As shown in Fig. 104, the time when the temperature rise of the device reaches saturation is changed by the light-emitting area, and it takes 10 minutes when the light-emitting area is small and the light-emitting area is wide. Therefore, it is necessary to prepare a memory amount that can grasp the current value from now to the past. Further, the time during which the current is saturated varies depending on the size of the device, the exothermic condition, and the material of the organic EL element, and therefore it may be necessary to grasp the current value for a longer period depending on the condition. Next, a method of controlling the amount of current will be described based on Fig. 105. As described above, the present invention suppresses the amount of current by controlling the number of scanning lines from the image data to control the lighting time. The method of controlling the number of horizontal scanning lines by the image data is to input the maximum number of lighting horizontal scanning lines 1〇5〇 and the minimum number of lighting horizontal scanning lines 1051 into the lighting rate control circuit 1〇54, by The 2 points of the difference, the relationship between the image data and the number of horizontal scanning lines is output, and the output data 1053 is output in response to the input data 1052 according to 94092-961016.doc -81 - 1295792. The calculation method can take the difference between 1050 and 1〇51 to calculate the slope based on the number of divisions of the image data. At this time, as in the case of 1〇6〇, if the difference between 1〇51 and 1〇5〇 is divided, the relationship will become a proportional relationship, and as the 丨〇6丨 is divided by the additional weight, the curve can also be drawn. As shown in Fig. 1 and 7, the present invention performs current suppression by controlling the circuits 1〇5〇 of 1〇5〇 and 1〇51 by the output value of 1〇24. The 1071 input of the input 1070 is the boundary value of the current suppression. When the output from 1024 is greater than 1071, the current suppression is performed, and the current suppression is not performed for 1 to 71 hours. As described above, the current suppression is performed by operating the maximum lighting horizontal scanning line number 1050 and the minimum lighting level scanning line number 1〇51. When the output of 1024 is larger than 1071, the output is reduced by the value of the maximum number of horizontal scanning lines by 1〇5〇 and the minimum number of lighting horizontal scanning lines by 101051, 72, 1073, so as to suppress the current, but as a method of reducing When it exceeds 1 1 , the method of lowering the value of 疋1, or calculating the difference between the output of 1024 and ι 71, lowers the value portion. The latter can finely control the amount of current suppression, so the accuracy of the suppression amount is improved. Also, when controlling 1050 and 1〇51, it is not necessary to make the reduction values the same. A method of reducing only 1050 as shown in FIG. 108 can also be considered. In Fig. 109, the relationship between the number of scanning horizontal scanning lines and the image data when the maximum lighting level scanning line number is 1〇5〇 and the minimum bright k level scanning line number 丨05丨 is controlled, and the current flowing into the device during control is controlled. A graph of the amount relative to the image data. 1093 is the case where the number of scan lines is not controlled at all. 1〇94 is the case of controlling the number of horizontal scanning lines of the children's lights. 1〇95 is the case of controlling ι〇5ΐ. The current is suppressed by the right time, and the input data becomes smaller. 94992-961016.doc -82- 1295792 Therefore, the result is 1024 output value 辔], the middle ▲ value is small, the current suppression value becomes smaller, or returns as The situation of 1090. Therefore, even if it is not known that the temperature is measured by an external circuit such as a thermistor, it is possible to perform a drive that suppresses the temperature rise only by the shadow. Moreover, since the temperature rises and the valley rises easily due to the concentration of one light, the use of the still image as the control value of 1051 and 1050 is also adopted by using the detection still image port 1 豕 < Deng Feng is a very effective means. The circuit diagram of the boundary time is shown in Fig. 110. If the above intermittent driving is performed, a spleen inserts black and can be made in an animation.

From time to time, the clear image of the wheel gallery is clear. However, the black insertion rate by intermittently driving right k冋' has a problem that the image will appear to be flickering. In particular, in displays using organic EL elements, unlike liquid crystal displays, the speed (or vice versa) in white is faster, so the flicker will appear more pronounced. As a method of suppressing flicker, there is a circuit configuration in which a private knife is cut in black during a still image which is easily seen to be flickering due to a circuit configuration as shown in Fig. 85 or when the black insertion rate is extremely high. To suppress the flicker. In short, this driving method is in the case of an animation in which only one part of the screen is moved: , and black is inserted regardless of the result, so that flicker is generated. It is extremely difficult to correctly judge the display state of an image, and this driving method cannot solve this problem. Because of A, a driving method is proposed as shown in FIG. 112 'When the black insertion rate enters a region causing flicker or is taken over by a black insertion to suppress flicker, and by maintaining a black insertion interval. Improved animation performance. As described above, when the organic EL display is intermittently driven, it is controlled by controlling electricity. Moreover, the transistor 11 d is controlled by the 17b outputted by the gate boat 12, so in order to control the black insertion rate, as long as the control (7) is 94992-961016.doc • 83 - 1295792 can be 0 in the present invention The frame is divided into 8 segments, and black insertion control is performed in units of blocks. In order to divide one frame into eight, each division is 125% of one frame. The reason for setting it at 12.5% was that the condition that the black insertion caused the flicker was that the black insertion rate around 15% to 25% began to see flicker, and the flicker was noticeably seen from 25% to 5%. In order to prevent the black insertion rate of the visible flicker from being above, the block of 12.5% is set so that one black block does not exceed 12.5%. 4 The range of flashing can be changed due to the size of the display, the brightness of the light, the frequency of the image, etc., so that the black insertion rate of the flashing is small, and the work frame can be divided into 16 segments (6.75%). When the black insertion rate is high, it is also possible to divide 1 frame by 4 (25%). The divided places are numbered as shown in FIG. This number indicates the order in which the lights are illuminated by the number of horizontal scanning lines. If the frame is divided by 8 as described above, the numbers are added in the order of 〇, 4, 2, 6, 1, 5, 3, and 7 as shown in Fig. 113'. Control 17b to start lighting sequentially by the apostrophe. Conversely, starting from the 7th, it becomes a non-lighting state, that is, black insertion. If the 1131 ’ black insertion is between 〇% and 12.5%, the block on the 7th is not lit. For example, i 132, from i2.5% to 25%, the block 7 will remain in the non-lighting state, and (4) will be in the non-lighting state. By this driving method, the black block is kept at a certain amount, and black insertion is performed in other places, and the animation performance can be maintained while suppressing the flicker. Fig. 114 shows the construction of the electric circuit for realizing this drive. As an example, the 鸭 次 进行 is divided into two η powers. When the number of lighting horizontal scanning lines 114 is formed, the comparison between the high level η bit u43 of the lighting horizontal scanning line number 142 and the lighting order 1144 is obtained. The lighting sequence U44 will pass the value of the count state of the horizontal sync signal positive number 94992-961016.doc -84 - 1295792, the value of the count state of 1 1 4 1 through the output value of the converter 1 1 46. 1143 is 1144 hours longer than the lighting sequence, and the signal 1145 from the output of the gate signal line 17b is controlled to output LOW. At this time, when 1145 is LOW, the lid is turned off. When the lighting sequence 1144 is the same as 1143, the HI output of the lower (N-n) bit value of 1142 is performed. When 1143 is larger than 1144, Π45 performs HI output. If this is done, as shown in Fig. 113, when there is a black insertion rate of 12.5% or more, at least 12% of black insertion can be ensured in one section, and animation performance can be maintained by performing a certain amount of black insertion. Lift while preventing flicker. At this time, the numbering is best prevented from flickering as shown in FIG. 113, but the present invention is not limited to this order. After all, the black insertion is selected by simply comparing the number of the division period with the size of the control line of the number of horizontal scanning lines. The place. Further, as shown in Fig. 115, after the amount of animation performance can be improved, the method of carefully inserting black is also effective. In general, in order to improve the dynamic performance, it is necessary to insert more than 25% of black, and if black insertion is performed once in a region of more than 5%, it is easy to cause flashing, so from 〇% to 5%, Black insertion is performed once, and after 50%, it is particularly preferable to drive the black insertion in a manner that does not cause flashing. Further, the converter 1146 has a method of creating a table for selecting an output value for an input value, and a method of sequentially replacing the high-order and low-order conversion circuits as shown in Fig. 122. The latter approach has the advantage of reducing the size of the circuit. Figs. 116, 117, 118, 119, 12, and 121 are circuit constituents for detecting a still image without using a frame body as shown in Fig. 7i. By using this circuit, it is possible to detect a still image without enlarging the circuit scale. With this circuit, the residual image of the organic EL can be prevented. 94992-961016.doc -85- 1295792 As described above, the organic EL has a life caused by deterioration of the element. As a cause of deterioration of the element, the temperature around the element or the current flowing into the element itself can be exemplified. As described above, the organic EL element is increased in temperature in proportion to the amount of current. In the display device using the organic EL element, the organic element is disposed in each pixel. Therefore, as the current amount of the organic EL device disposed in each pixel increases, the EL element emits light, and the entire display temperature rises, resulting in deterioration of the element. . Therefore, in the case of the display using the organic EL element, it is necessary to suppress the current flowing into the organic EL element in the case where the amount of heat generated by the entire display is increased. As described above, as a method of suppressing the amount of current of the organic EL element, there is a method of controlling the light-emitting time of the organic EL element with respect to the input data as shown in FIG. By controlling the light-emitting time of the organic EL, the current amount is controlled, the amount of heat generation is reduced, and the life is improved. However, since the amount of current flowing into the organic EL element is also one of the causes of deterioration of the element, if the amount of current flowing into the element itself is reduced as shown in FIG. 123, the driving of the current 减少 of the entire display can be reduced, and the element can be further prevented. Deterioration. The method of suppressing the current amount of the inflow member itself is as long as the source driving is suppressed: 2, 4, in order to flow a current into the reference current line of the driving transistor Ua, the electric current can be made. As means for suppressing the amount of current of the reference current line 629, there is a method in which the resistor for making the voltage of the reference power source line 636 becomes a variable resistor and operates as the resistance itself. Further, as shown in Fig. 62, in the source driver, the electron amount 625 which is the operation reference current, and the operation electron amount 625, Fig. 124 shows the circuit configuration in which the amount of electrons is used to control the amount of current. The circuit 1241 of the total display display data determines the image data, and inputs a current 94992-961 〇i6.d < 1295792 suppression circuit 1242. The current suppression circuit is a circuit for calculating the lighting rate as in 550, or a circuit having a delay circuit as in 612, or a circuit for suppressing the horizontal scanning line number of the current from the input data. The electronic quantity control circuit 1244 can be controlled by switching the signal line for controlling the number of scanning horizontal scanning lines by the switching circuit 1243 without controlling the number of scanning lines of the lighting level and controlling the amount of current by the electronic quantity. Further, at this time, by controlling the signal line 1245 of the current suppression method in the electronic quantity control circuit (conversion circuit) 1244 so as to scan the line number or the electron amount in the lighting level, the control current amount can be formed. The circuit is constructed. 0 However, the method of suppressing the reference current by the amount of electrons or the like and suppressing the amount of current has disadvantages. As will be described, the floating capacitor 45 is present in the source signal line 丨8. In order to change the source signal line voltage, the charge of the floating capacitor must be pulled out. The time Δ T taken for this pull-out is Δ Q (the charge of the floating capacitor) = 1 (the current flowing into the source signal line) χ Δ Τ = (: (floating capacitance value) χ Δν. Since the gradation is lower, the value becomes The smaller the size, the more difficult it is to pull out the charge of the floating capacitor 451. Therefore, the problem of changing the signal before the specific party degree into the inside of the pixel is more apparent in the _low gradation display. Therefore, if the amount of electrons is used to suppress the reference current amount When the low gradation is not displayed, the above problem occurs more prominently, so it is difficult to maintain gradation in the low gradation portion. Therefore, the present invention proposes to convert the input data itself as shown in FIG. The method of reducing the amount of current to reduce the amount of current. Since the gradation of the data is reduced, the gradation of the gradation becomes small, but in the low gradation portion, since the output of the source driver 14 itself does not become small, the above Floating 94092-961016.doc -87- 1295792 The writes caused by the travel capacitors disappeared. However, the amount of data is reduced, that is, the Thundering 流入 流入 into the organic EL element Small, so it can prevent components from being inferior The small amount of fine bait can also be reduced by the maximum gray scale. As shown in Figure 125, the maximum gray level is reduced from X to χ/4' by the total amount of input data. The amount is suppressed to 1/4. η" is a graph showing the other gradations when the maximum number of gradations is reduced. By reducing the maximum gradation to 1/4, the intermediate gradation to the same is also reduced. Therefore, generally, the difference in current amount per gradation of the gradation system is increased, so if the image is displayed with a small degree of redundancy, a problem of seeing a contour is generated. However, the maximum gray is driven by this. Although the degree is reduced, the amount of current per gradation does not change, so even if the number of gradations is reduced, the pseudo contour is not generated. As a method of reducing the amount of data, there is a conversion of the input data by the conversion shown in FIG. The method of performing the gamma curve is performed by using a gamma curve conversion circuit having a plurality of vertices. As shown in Fig. 126, the vertices when the current I is not suppressed are 1261a, 1261b...126lh. Set in order to make the data like 1262a, 1262b··· 12 62h reduction point. The current suppression value 1264 is decomposed and connected to the line of the respective vertices and re-wired, so that a gamma curve like 1263 can be generated, and the ratio of the output data to the input data can be maintained, and the entire data can be uniformly Since 1262a, 1262b...1262h is 0, it is only necessary to divide the control value by the value of 1261a, 1261b...l261h, so the value of 1262a, 1262b···1262h is preferably 0. However, the present invention does not Limit the value of 1262a, 1262b...1262h to 〇, assuming that the value of 1262a, 1262b." 1262h is set to 1 /2 of the value of 1261a, 1261b··· 1261h, and the current value can only be decreased regardless of any control. The method is limited to 1 /2, 94992-961016.doc -88- 1295792. As mentioned above, by suppressing the suppression of the rate of the data itself... The motor suppression method of the 枓 itself has the effect of preventing the deterioration of the component by the suppression method of controlling the lighting, and the neighboring eight-face ice 1 士仁 has 1 material itself. The disadvantage of the reduced gray scale range that can be expressed. Further, the suppression method for controlling the lighting rate as before has the advantage of being an intermittent driving and having an animated two liters, and the gradation can be maintained. Therefore, the method of suppressing the control of the lamp rate is excellent in displaying images. Therefore, the present invention proposes a method of suppressing the amount of current by controlling the lighting rate until the amount of suppression is controlled as shown in Fig. 127, and thereafter suppresses the driving of suppressing the amount of current by reducing the data itself. The waveform of Figure 127 is taken as an example. In Fig. 127, the current suppression amount is controlled by controlling the lighting rate until 1/2, and the remaining 1/2 to 1/4 of the suppression suppresses the f flow rate to 1/1 by suppressing the data itself. 4 so far. Since the data is reduced to 1/2, it is assumed that the data is expressed in octaves, and only the gradation of 7-bits can be expressed. However, the amount of data per pixel of the clamshell lamp area is large, making it difficult to judge gray. The area of the degree, so reducing the gray level is not a disadvantage. When this driving is performed, in the case of displaying the white gloss of 100% of the xenon lamp rate, the amount of current flowing into the pixel instantaneously becomes 1 /2, which is 2 times as compared with the case of controlling only during the lighting period, although the amount of current is the same. The above prevents deterioration of the element. Fig. 128 shows the circuit configuration for realizing the present invention. In 1281, it has a structure for calculating the state of the image by calculating the data input from the outside. The 丨282 has a configuration that controls the amount of current by the data output from 1281, and 1283 has a gamma curve. The gamma curve generated at 1283 is input to the gamma conversion circuit 1284. The input data RGB is converted by this gamma curve 1284, and input 94092-961016.doc -89-1295792 into the source driver 14. The 1285 system has the output of 1282 assigned to the lighting horizontal scanning line number control and gamma curve control The composition. The control value of the number of horizontal scanning lines is input to the gate driver 12, and the control value of the gamma curve is input to 1283. It is assumed that the output of 1282 controls the total current amount to 1/4, and then at 1285, the horizontal scanning is performed. The number of lines is controlled to be converted at 1/2, and the gamma curve is controlled at 1/2 for conversion. Thereby, the total current amount is 1/4. Various current suppression methods can also be realized by changing the ratio of the horizontal scanning line number control and the gamma curve control assigned to the lighting level at 12 8 5 . In addition, there is also a method of reducing the amount of reference current instead of reducing the data itself. When this method is employed, there is a problem of insufficient writing due to the floating capacitance as described above, but it is technically possible. Further, the circuit configuration is complicated, but it can also be used in combination with a method of reducing the data itself or a method of controlling the number of horizontal scanning lines. The present invention is applicable to a controller IC for driving a display device, and the controller 1C also includes a DSP having a high computing function, and also includes an FPGA. Figure 34 is a cross-sectional view of the viewfinder of the present embodiment. However, it is schematically described for ease of explanation, and there is a part of enlargement or reduction, and it is easy to omit. For example, in Fig. 34, the eye cover is omitted. The above matters are also applicable to other drawings. The back surface of the body 344 is dark or black, in order to prevent the fog emitted from the el display panel (display device) from being reflected on the inner surface of the body 344, causing a decrease in display contrast. Further, a phase plate (again/four plates, etc.) 1〇8, a polarizing plate 109, and the like are disposed on the light emitting side of the display panel. The magnifying glass 342 is mounted on the eyelet ring 341, and the observer can change the insertion position of the eyelet ring 341 94992-961〇i6.d〇c -90-1295792 in the body 344 to adjust so that the display image 50 of the display panel 345 has focus. Further, the right lens 343 is disposed on the light exit side of the display panel 345 as needed, and the main ray incident on the magnifying glass 342 can be collected. Therefore, the lens diameter of the magnifying mirror 342 can be reduced, and the viewfinder can be miniaturized. Figure 52 is a perspective view of the camera. The camera includes a photographing (imaging) lens unit 552 and a camera main body 344, and an eye contact cover is attached to the rear side of the photographing lens unit and the viewfinder unit (see also Fig. 34). The observer (user) thereby picks up the cover and observes the orientation 50 of the display panel 345. In another aspect, the EL display panel of the present invention is also used as a display monitor, and the display unit 5 can use the fulcrum 52 to freely define the angle. When the display unit 50 is not used, it is stored in the storage unit 523. Switch 524 implements the switching or control of the following functions. The switch is similar to the "mode" switch, and the switch 524 is also suitable for installation in a mobile phone or the like. The display mode switch 524 is explained. The above switching operation is used when the power of the mobile phone or the monitor is turned on. The display screen 50 is displayed very brightly, and after a certain period of time, the saving circuit is made to reduce the display brightness. Further, it can be used as a function of setting the brightness desired by the user. For example, if you are outside the house, you will be exempted from the book because the outside is bright outside and the picture is completely invisible. However, if the display is continued with high brightness, the rainbow element 15 will rapidly deteriorate, so that it is very bright, F ^ , and the condition of the child, returning to the normal brightness during the time and constructing it in the south. When displayed, the user can lift 94992-961016.doc -91- 1295792 by pressing the button. Therefore, the user should be able to switch with the switch (button 524), or can be automatically changed in the setting mode, or detected. External light is automatically switched to form. Further, it is preferable that the user or the like can set the display brightness to write, 6 g%, and 8 g%. Further, the display surface 50 is preferably a Gaussian distribution display, and the Gaussian distribution is a mode in which the brightness of the central portion is bright and the peripheral portion is dark. Visually, as long as the central part is bright, even if the peripheral part is dark, it still feels bright. According to the subjective evaluation, as long as the peripheral portion maintains a brightness of 7〇% as compared with the central portion, it is visually inferior to the brightness of the step-down of 5〇%, which does not substantially pose a problem. Furthermore, the Gaussian distribution display should be provided with a switch that can be turned on and off. For example, if Gaussian display is performed outside the house, the periphery of the screen will be completely invisible, so the user should be able to switch with the button, automatically change in the setting mode, or detect. The external light is automatically switched and configured. Further, it is preferable that the user or the like can set the display brightness to 50%, 60%, or 80%. The liquid crystal display panel generates a fixed Gaussian distribution by the backlight, so that the Gaussian distribution cannot be turned on and off, and the Gaussian distribution can be turned on and off, which is a characteristic of the self-luminous display device. # Further, when the frame rate is specified, it may interfere with the lighting status of the indoor fluorescent lamp, etc., and flicker may occur. In other words, when the fluorescent lamp is turned on at 6 Hz, if the organic EL element 15 operates at a frame rate of 60 Hz, subtle interference will occur, and the surface may be slow and dark. To avoid this, change the frame rate. The present invention is a function of changing the additional frame rate. The above functions are realized by the switch 524. The switch 524 is activated in accordance with the function table of the display screen 50, so that the switching of the functions described above can be realized. 94992-961016.doc -92- 1295792 Furthermore, the above matters are not limited to mobile phones, and of course can also be applied to televisions and monitors. Moreover, in order to enable the user to immediately recognize what state is in the state, it is preferable to display the figure q, one port eight Ucon). The above matters are the same for the following items. This embodiment of the EL display dreams | 1 > Be not display can be applied not only to the camera, but also to the electronic phase shown in Figure 5, <electrical stack, digital camera. The display device is used as a device view 50 attached to the camera body 5 3 1 . A switch 524 is attached to the camera body 531 except for the shutter 533. In the above, the display area of the panel is small, but if it is larger than the above, the screen 5 is easily trapped. For the countermeasure, the present invention is as shown in FIG. 54 and the outer frame 541 is attached to the display panel. And fixing member 544 is installed so that outer frame 541 can be suspended. This fixing member 544 is attached to a wall or the like. However, since the screen size of the display panel is increased and the weight is also increased, the foot mounting portion 543 is disposed on the lower side of the display panel, and the weight of the display panel can be maintained by the plurality of legs 542. As shown in A, the foot 542 can be moved left and right, and the foot 542 is formed as shown in B, and can be contracted to constitute 'so that it can be easily set even in a narrow place. The television of Fig. 54 covers a protective film (protective plate) for protecting the surface of the screen, which is one of the objects for preventing the object from coming into contact with the surface of the display panel. An AI-R film is formed on the surface of the protective film, or by engraving the surface to suppress the display panel from being printed on an external condition (outer light). It is formed by dispersing beads or the like between the protective film and the display panel so as to be arranged with a certain space. Further, a fine convex portion is formed on the back surface of the protective film, and 94992-961016.doc -93- 1295792 is held between the display τ panel and the protective film. By keeping the space in this way, the impact from the protective film is suppressed from being transmitted to the display panel. It is also effective to arrange or inject a liquid binder such as a liquid such as ethanol or ethylene glycol or a solid resin such as an acrylic resin or an epoxy resin between the film and the display panel. This is because the interface reflection can be prevented while the aforementioned photo-binding agent acts as a buffer material. As the protective film, a polycarbonate film (plate), a polypropylene film (plate), an acrylic film (plate), a polyester film (plate), a PVA film (plate), and the like are exemplified. Of course, other proprietary resin films (ABS, etc.) can also be used. Also, it is also possible to form an inorganic material such as m glass. In place of the protective film, the same effect can be obtained by coating the surface of the display panel with a thickness of 〇·5 mm or more and 2 mm or less in an epoxy resin, a scented resin, or an acrylic resin. X, such as engraving on the surface of such a resin, is also effective. Further, since the dirt adhering to the surface can be easily wiped off with the detergent, it is also effective to apply a gas film on the surface of the protective film or the film material. Further, a protective film is formed thicker and can be used together with the front light. The display panel of the embodiment of the present invention can also be combined with the three-sided open structure, and is particularly effective when the three-side open structure pixel is fabricated by an amorphous germanium technique. Further, in a panel formed by an amorphous germanium technique, since it is impossible to control the process of changing the characteristics of the crystal element, it is preferable to implement the double pulse driving, the reset driving, the dummy pixel driving, and the like of the present invention. In summary, the transistor 11 and the like of the present invention are not limited to those by the polysilicon technology, and may be made by an amorphous germanium technique. In summary, in the display panel of the present invention, the transistor 11 constituting the pixel 16 can also be a transistor formed by an amorphous germanium technique. Further, 94992-961016.doc • 94· 1295792 Of course, the gate driver 12 and the source driver 14 may also be formed or constructed using an amorphous germanium technique. The technical idea described in the embodiments of the present invention can be applied to a camera, a projector, a stereoscopic television, a projection television, and the like. Also, it can be applied to a viewfinder, a mobile phone monitor, a PHS, a portable information terminal device and its monitor, a digital camera, and a monitor thereof. It can also be applied to electronic photo systems, Head M〇unt Display, direct-view monitor displays, notebook PCs, cameras, and electronic digital cameras. Also, a cash dispenser, a public telephone, a television telephone, a personal computer, a watch, and a display device thereof. Further, of course, it is also possible to apply or develop display monitors for home electric appliances, pocket game machines and monitors thereof, backlights for display panels, lighting devices for home use or business use, and the like. The lighting device should preferably be constructed to vary color temperature. In this case, pixels of RGB are formed in a stripe shape or a dot matrix shape, and the color temperature can be changed by adjusting the current flowing into it. Further, it can be applied to display devices such as advertisements and posters, rgb annunciators, alarm display lamps, and the like. Moreover, as a light source of the scanner, the organic display panel is also effective. A dot matrix of Rgb is used as a light source, and light is irradiated onto an object to read an image. Of course, monochrome is also available. Further, it is not limited to the active matrix, and a simple matrix is also possible. If the color temperature can be adjusted, the image reading accuracy is also improved. Further, the organic EL display device is also effective for the backlight of the liquid crystal display device. The pixels of RGB of the EL display device (backlight) are formed in a stripe shape or a dot matrix shape, and the color temperature can be changed by adjusting the current flowing in, etc., and the shell degree can be adjusted. In addition, since it is a surface light source, it is easy to form a Gaussian distribution in the peripheral portion of 94992-961016.doc -95 - 1295792 :=. Further, the liquid crystal display surface B of the field sequential method is also known to be effective in black insertion of the moonlight even if the backlight is bright and dark. The backlight of the liquid crystal display panel is used. ', can be used as a dynamic display from = this: -: it: in order to perform the above-mentioned functions of the present invention by computer, the function of the drive circuit, components, etc. of the first display device, and the electric cat = Part of the means (or exhibition, the program of the present invention is for::: the program of action. Γ: = set: all or part of the method of the step _ process, I and = the program that works together with the computer. The invention is: The recording of the media is carried out by the computer to execute the above-mentioned book; / set = all or part of the driving circuit of the display device: Take the aforementioned process (4) computer reading, and reading the body. a program for performing the above-described functions of the recording medium, which is operated by a computer, and which is executed by a computer (or all or part of the steps of the driving method of the process, and the reading: 乍, etc.) Read by computer, recorded (4) the program and the computer work together to perform the aforementioned functions

Furthermore, the present invention, $b, +, ΓA, means that the two stages (or devices, components, etc.) of the remedy are "partial steps (or one or several means of the work, the above-mentioned ones of the present invention) "After a few steps, a function, etc." means that the above-mentioned plural steps 94092-961016.doc -96- 1295792 and the above-mentioned "functions of means (or devices, components, etc.)" mean the foregoing The "step (or sequence action)" of the present invention means all or part of the actions of the foregoing steps. The private-use state of this month can also be recorded in a recording medium that can be read by a computer, and the same as the electric material. Moreover, one of the programs of the present invention can also be transmitted to a transmission medium, and is read by a computer to interact with a computer to operate. Further, the recording medium includes a ROM, etc., and includes a transmission medium such as a network, a light wave, a sound wave, and the like as the transmission medium. The computer of the present invention is not limited to a hardware such as a CPU, and may include a firmware or an OS or even a periphery. machine. Furthermore, as described above, the composition of the present invention can also be f| &g& g [Industrial Applicability] The present invention shows that if the brightness of the image is high, the current flowing into the panel is reduced to the right. When the amount of current is applied to the day, the organic component or the battery is more continuously protected, and the entire pixel is bright, so that the practical effect is large. Further, the display panel and the display device of the present invention are composed of high image quality, good animation display, low lightning consumption, such as: A, Shi π Gu Shishi - low cost, and the same shell. Play a characteristic effect. Further, according to the present invention, it is possible to constitute a low-power consumption information display device or the like, and therefore it is possible to reduce power and size, and therefore it does not consume resources. Moreover, even if the display panel of the fine-grained display panel is fully compatible, it is good for the 94992-961016.doc -97- 1295792 earth environment and the cosmic environment. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a view showing a pixel configuration of a display panel of the present invention. 2 is a view showing a pixel configuration of a display panel of the present invention. 3(a) and 3(b) are flowcharts showing the driving of the present invention. Fig. 4 is a view showing a driving waveform of the present invention. Θ 5(a) and (b) are descriptions of display areas of the display panel of the present invention. Fig. 6 is a view showing the configuration of a pixel of a display panel of the present invention. Fig. 7 is an explanatory view showing a method of manufacturing a display panel of the present invention. Figure 8 is a block diagram of a panel of the present invention. Fig. 9 is a view showing the relationship between the source signal line and the gate signal line. / Capacitance Figure 10 is a cross-sectional view of the display panel of the present invention. Figure 11 is a cross-sectional view showing a display panel of the present invention. Figure 12 is a graph showing the relationship between the amount of current of the source line and the brightness of the panel. 13(a) and 13(b) are explanatory views of the display state of the display panel. Fig. 14 is a view showing a driving waveform of the present invention. Fig. 15 is a view showing a driving waveform of the present invention. Weeks 16(a) and (b) are explanatory diagrams of the display state of the display panel. Fig. 17 is a view showing a driving waveform of the present invention. Fig. 18 is a view showing the driving waveform of the present invention. 19(a1) to (c3) are explanatory views of the display state of the display panel. 20(a) and (b) are explanatory views of the display state of the display panel. Figure 21 is a diagram showing the driving waveform of the present invention. 94992-961016.doc -98- 1295792 Fig. 22 (a) and (b) are explanatory views of the display state of the display panel. Figure 23 is a view showing the driving waveform of the present invention. Figure 24 is a diagram showing the relationship between the pixel configuration and the battery. Figure 25 is a graph showing the relationship between the brightness of the area and the amount of current. Figure 26 is a graph showing the relationship between input data and current amount in the present invention. Figure 27 is a circuit diagram of the present invention. Fig. 28 is a graph showing the relationship between the brightness and the amount of current in the display area when the lighting rate control drive is applied.

Fig. 29 is a diagram showing a control method of the lighting rate control drive. Fig. 30 is a diagram showing a control method of the lighting rate control drive. Figure 31 is a graph showing the relationship between the lighting rate and the brightness. A circle represents a diagram of the driving waveform of the present invention. Figure 33 is a graph showing the relationship between the light-emitting rate and the brightness which are not modified according to the present invention. Figure 34 is an explanatory view of the viewfinder of the present invention. Figure 35 is an explanatory view showing a display state of the present invention. Figure 36 is a diagram illustrating the merging with the source signal.

Figure 37 is a graph showing the relationship between lighting rate and coupling. Fig. 38 is a movement diagram of the lighting rate when the input data is greatly shaken. Figure 39 is an explanatory view of the < Π墚 Π墚 method according to the present invention. Figure 40 is a current transfer diagram for a special image mode. Figure 41 is a drive diagram of the battery protection of the present invention. Fig. 42 is a graph showing the relationship between the amount of current when the black display is turned into a white display. Figure 43 is a structural diagram of the road of the present invention. Figure 44 is an explanatory view showing one state of the present invention. 94992-961016.doc -99- 1295792 Figs. 45(a) and (b) are circuit diagrams of the present invention. Figure 46 is a circuit diagram of the present invention. Fig. 47 is a driving waveform diagram of the N-fold pulse driving. Fig. 48 is a driving waveform diagram of the N-fold pulse driving. Fig. 49 is an explanatory diagram showing n-time pulse driving in the low luminance portion. Figure 50 is an explanatory view of the driving of the present invention. Fig. 51 is an explanatory diagram of n-time pulse driving in the low-luminance portion. Figure 52 is an explanatory view of a camera of the present invention. Figure 53 is an explanatory view of a digital camera of the present invention. Figure 54 is an explanatory view of a television (monitor) of the present invention. Fig. 55 is a circuit diagram showing the lighting rate control drive. Figure 56 is a timing diagram of the lighting rate control drive. Figure 5 7 is a timing diagram of the lighting rate control drive. Figure 58 is a circuit diagram showing the lighting rate delay adding circuit. Figure 59 is a graph of the delay rate and the necessary number of turns. Fig. 60 is a circuit diagram showing the lighting control rate of the light control rate. Fig. 61 is a circuit configuration diagram of a lighting rate delay adding circuit. Figure 62 is a block diagram of the source driver. Fig. 63 is a view showing the configuration of a source driver. Fig. 64 is a circuit diagram showing a driving method of driving a double pulse in a low luminance portion. Fig. 65 is a circuit diagram showing a driving method of driving a double pulse in a low luminance portion. Figure 66 is an illustration of a gamma curve. 94992-961016.doc -100- 1295792 Figure 67 is an illustration of the gamma curve. Fig. 68 is a circuit configuration diagram of a gamma curve. Figure 69 is a circuit diagram of the invention. Figure 70 is a block diagram showing the structure of a temporary memory used in the present invention. Figure 71 is a circuit diagram of the present invention. Fig. 72 is a view showing a display state. Figure 73 is a circuit diagram of the present invention. Figure 74 is a block diagram showing the structure of a temporary memory used in the present invention. Figure 75 is a timing diagram of the present invention. Figure 76 is a diagram showing the configuration of a pixel of the present invention. Figure 77 is a circuit diagram of the present invention. Figure 78 is a timing diagram of the present invention. Fig. 79 is an explanatory view showing a display state of the mounting panel of the present invention. Fig. 80 is an explanatory view showing the display state of the mounting panel of the present invention. Fig. 81 is an explanatory view showing a display state of the mounting panel of the present invention. Figure 82 is a timing diagram of the present invention. Figure 83 is a timing diagram of the present invention. Figure 84 is a timing diagram of the present invention. Figure 85 is a circuit diagram of the present invention. Figure 86 is a timing diagram of the present invention. Figure 87 is a timing diagram of the present invention. Figure 88 is a timing diagram of the present invention. Fig. 89 is an explanatory view showing a display state of a mounting panel of the present invention. Fig. 90 is an explanatory view showing a pixel configuration. 94992-961016.doc 1295792 Figure 91 is a graph showing the relationship between temperature and lifetime of an organic EL device. Fig. 92 is a graph showing the relationship between the state of the device in use and the light rate of the device and the reference current value of the current of the flow signal line. Figure 93 is a graph showing the relationship between the state of the device at the time of use of the present invention and the amount of current flowing into the device. Figure 94 is a graph showing the relationship of the amount of luminescence of a pixel when used in the present invention. Figure 95 is a circuit diagram of the present invention. Figure 96 is a circuit diagram of the present invention. Figure 97 is a graph showing the relationship between the lighting rate and the current value. Figure 98 is a circuit diagram of the present invention. Figure 99 is a circuit diagram of the present invention. Fig. 100 is an explanatory view showing a display state of a mounting panel of the present invention. Fig. 101 is an explanatory view showing a display state of a mounting panel of the present invention. Figure 102 is a circuit diagram of the present invention. Figure 103 is a circuit diagram of the present invention. Figure 104 is a graph showing the relationship between the temperature rise rate of the device. Figure 105 is a circuit diagram of the present invention. Figure 106 is a graph showing the relationship between the input data and the number of horizontal scanning lines. Figure 107 is a circuit diagram of the present invention. Figure 108 is a graph showing the relationship between the input data and the number of horizontal scanning lines. Figure 109 is a graph showing the relationship between the temperature rise of the input data. Figure 110 is a circuit diagram of the present invention. Figure 111 is a circuit diagram of the present invention. Figure 112 is a timing diagram of the present invention. 94992-961016.doc 1295792 Figure 113 is a timing diagram of the present invention. Figure 114 is a circuit diagram of the present invention. Figure 115 is a timing chart of the present invention. Figure 116 is a circuit diagram of the present invention. Figure 117 is a circuit configuration diagram of the present invention. Figure 118 is a circuit diagram of the present invention. Figure 119 is a circuit configuration diagram of the present invention. Figure 120 is a circuit diagram of the present invention. Figure 121 is a circuit diagram of the present invention. Lutu 122 is a diagram showing a conversion method of a converter of data. Figure 123 is a graph showing the relationship between input data and current. Figure 124 is a circuit diagram of the present invention. Figure 125 is a plot of input data versus maximum gray level. Figure 126 is a diagram showing the conversion of a gamma curve. Fig. 127 is a diagram showing the relationship between the suppression of the amount of current and the control of the maximum gradation number and the control of the illumination rate. Figure 128 is a circuit diagram of the present invention. Figure 129 is a diagram showing the method of conversion of the subject matter of the present invention. Figure 130 is a diagram of input data and display of the lighting rate or classification thereof. Figure 131 is a circuit diagram of the present invention. Figure 132 is a diagram showing the pixel configuration of a display panel of the present invention. Figure 133 is a diagram showing the configuration of a pixel of a display panel of the present invention. Figure 134 is a graph showing the delay of the change in the lighting rate. [Description of main component symbols] 94992-961016.doc -103- 1295792 1Bu 12 14 15 16, 17, 18 19 50 51 52 53 61 62 63 65 71 72 73 74 81 82 83 84 1331 Transistor (thin film transistor, TFT) Gate driver (gate driver 1C circuit) Source driver (source driver 1C circuit) EL device (light-emitting device) 1336 Pixel 1337 Gate signal line source signal line storage capacitor (additional capacitor, additional capacitor) Display 昼Surface write pixel (write pixel column) Non-display pixel (non-display area, non-light area) Display pixel (display area, lighting area) Offset register inverter (OEV signal line) Output buffer OR Circuit array substrate (display panel) Laser irradiation range (excimer laser point) Positioning marking machine glass substrate (array substrate) Control 1C (control 1C circuit) Power supply 1C (power supply 1C circuit) Printed substrate flexible substrate 94992- 961016.doc 1295792 85 Sealing cap 86 Cathode wiring 87 Anode wiring (Vdd) 88 Data signal line 89 Gate control signal line 91, 451 Floating capacitor 101 Wall (rib) 102 Interlayer Insulating film 104 contact point connecting portion 105 pixel electrode 106 cathode electrode 107 desiccant 108 λ /4 plate 109 polarizing plate 111 thin film sealing film 271 dummy pixel (false pixel column) 341 eye ring 342 magnifier 343 convex lens 452 current source 481a horizontal synchronizing signal HD 482a, 483a Gate control signal 521 Pivot (rotating part) 522 Photographic lens 94092-961016.doc -105- 1295792 523 Storage part 524 Switch 531 Main body 532 Photographing section 533 Shutter switch 541 Mounting frame 542 Foot 543 Mounting table 544 Fixing part 621 Resistor 622 Operational Amplifier 623 Transistor 624 Resistor 625 Voltage Regulation 626 Power Line 627 Switching Mode (Switch) 628 Control Data 629 Reference Current Line 94092-961016.doc - 106-

Claims (1)

1295792, the scope of patent application: f乂year f month%曰修(more)本本+卜》电_ A method of driving a self-luminous display device, which is composed of a plurality of self-illuminating 70 pixels in the pixel row direction The pixel column direction is arranged in a matrix shape to flow a current between the anode electrode and the cathode electrode of the respective light-emitting elements, so that the respective pixels emit light for driving the display portion; and: by the first processing, the system corresponds to Obtaining a predetermined single amount from the externally input image data to obtain a first current amount ' flowing between the anode electrode and the cathode electrode and the first current amount is not in accordance with the image resource: value distribution state around the image data The processor of the value; the second process 'the money line corresponds to the image data from the external input, and the second motor is to be flown into the second motor between the anode electrode and the cathode electrode' and the second current quantity is Preparing (10) suppressing the value of the first current amount by a specific ratio in the distribution of the image data values around the image data, and the foregoing The suppression ratio is determined by the processor having the variable distribution of the image data values; and t controlling the amount of current flowing into each of the pixel columns in accordance with the result of the second or the second processing means to cause the display portion to emit light. 2. The driving method of the self-luminous display device of the requester, wherein the gray value of the image data input from the outside is smaller than the first specific gray value on the low gray side for black display, by the foregoing The treatment determines the first current amount applied between the anode electrode and the cathode electrode of the corresponding respective light-emitting elements. 3. The driving method of the self-light display device of claim 1, wherein the gray value of the image data input from the external 94992-961016.doc 1295792 is higher than the first specific gray value in order to display the white display On the gradation side, the second current amount X applied between the anode electrode and the cathode electrode of the corresponding respective light-emitting elements is determined by the second processing, and at this time, the gradation value is set for the gray value. When the first current amount in the first processing is ^, the relationship between the first current amount y and the second current amount X is established as follows: 0.2 〇 yg 〇 · 6 〇 γ. The driving method of the self-luminous display device according to any one of claims 1 to 3, wherein the amount of applied current is obtained by obtaining a current value i of a maximum value of the image data input from the outside during the first period. 1. The image data obtained by the second period is calculated by calculating an appropriate current value i2, and the ratio is calculated according to the ratio ι2 Λ 1, and sequentially applied to the specific image data input according to the second period input. The processing of the current amount of each of the above pixels is determined. 5. The driving current set of the self-luminous display device according to any one of claims 1 to 3, wherein the applied current amount is obtained by obtaining a third current value 丨3 of the maximum value of the input image data, An actual current is actually applied between the anode electrode and the cathode electrode of each of the light-emitting elements, and an optimum value is obtained. The value is used as the second current value 丨4, and the ratio 丨4/丨3 is multiplied to the input image data. In order to sequentially calculate the amount of current applied to each of the aforementioned pixels displayed according to the specific pattern data. The driving method of the self-luminous display device according to any one of the preceding claims, wherein the grayscale value of the image data input from the outside is higher than the first specific grayscale value on the high grayscale side for white display The amount of current applied between the respective electrode electrodes is controlled by black insertion rate 94092-961016.doc 1295792. A method for driving the anode electrode and the cathode self-luminous display device described above, wherein the black= is sequentially carried out from the column to the terminal column, and the black is inserted once in the “8. 9. Self-luminescence as in claim 7 The driving method of the display device, wherein the first row = the first column sequentially proceeds to the terminal column, and the black region is divided into a plurality of regions to be inserted in the foregoing. The driving method of the self-luminous display device of claim 6 , wherein the black insertion is not to divide the black area into a plurality of area insertions in the U ,, and is sequentially performed from the first column to the last (four), but the side replacement order is inserted 0 0 · as in the request items 1 to 3 φ / ^ ^, the driving side of the self-illuminating display device of any one of the main 3'', wherein the gray value of the aforementioned image data input from the 彳 part is higher than the first-order, and is higher than the high-gradation for white display. On the side, the amount of current applied between the anode electrode and the cathode electrode applied to each of the light-emitting elements described above is controlled by adjusting the amount of current flowing into the source line group. The driving method, wherein the adjustment of the current amount flowing into the source line group of the month is performed by increasing or decreasing the reference current value. 12. The driving method of the self-luminous display device of claim 10, wherein the inflow is described The aforementioned adjustment of the amount of current of the source line group is performed by increasing or decreasing the number of gradations. 13 · The driving method of the self-luminous display device according to any one of items 1 to 3 is 94992-961016.doc 1295792 And obtaining a difference knife between the first current flowing between the anode electrode and the cathode electrode of the respective light-emitting elements during the first frame period and the second current flowing during the second frame period of the first frame period; The operation is such that the difference value is l/n (n is a number of 1 or more) in the differential current value, and the selected value of the pixel column is determined by the η differential current value. 14. 15. 16. 17. 18. 19. The driving method of the self-luminous display device, wherein the aforementioned value is 4$ 256. The driving method of the self-luminous display device according to any one of claim 13 is characterized in that the anode electrode flows into the aforementioned respective light-emitting elements and the foregoing The amount of current between the cathode electrodes is corrected to a constant of 7 constants. For example, the driving method of the self-luminous display device of claim 15, wherein the 7 constants are on the curve formed by sequentially combining the intermediate values of the complex y curves. The method of driving a self-luminous display device according to claim 15, wherein the increase or decrease of the 7 # number is adjusted by the length of the light-emitting period of the self-luminous element. As in the claims 1 to 3, the #-item a driving means of the self-luminous display device, wherein the switching means for the foregoing processing means is arranged, and the switching of the first processing is controlled to facilitate the timing of the combination of the first processing and the second processing The amount of current flowing between the anode electrode and the cathode electrode before the respective light-emitting elements of the current source is determined by the first process to determine the amount of current flowing between the anode electrode and the cathode electrode of the respective light-emitting elements. A driving circuit for a self-luminous display device, which is arranged in a matrix in a pixel row direction and a pixel column direction by a plurality of self-luminous elements constituting each image 94092-961016.doc 1295792, and current flows to the respective light-emitting elements Between the anode electrode and the cathode electrode, so that the respective pixels emit light for driving the display portion; and: a first-light-emitting means for pre-setting the degree of the image corresponding to the image data input from the outside to make the respective a light-emitting element illuminator; and a first illuminating means for adjusting the illuminance brightness distribution of each of the surrounding pixels to suppress the aforementioned first-brightness <RTIgt; The second brightness of I causes the aforementioned respective light-emitting elements to emit light. 2. A driving circuit for a self-luminous display device in which a plurality of (four) optical elements constituting each pixel are arranged in a matrix in a pixel row direction and a pixel column direction, and a current is supplied to an anode electrode of each of the respective light-emitting elements. And a cathode electrode for causing each of the pixels to emit light for driving the display portion; and: a first processing means for performing image data corresponding to the external input, and setting between the anode electrode and the cathode electrode a first current amount, and the first current amount is not a processor that sets a predetermined single value according to a distribution of image data values surrounding the image data; and the second processing means performs the foregoing corresponding to the external input The image material is set to flow into the second current amount between the anode electrode and the cathode electrode, and the second current amount is formed according to the distribution of the image data values around the image data 94092-961016.doc 1295792. The value of the first current amount, and the distribution of the previous data value is variable; brother, prepare one special The proportional ratio suppression ratio according to the above-mentioned image, and the means of treatment are based on the above-mentioned first and the gentleman's lack of seat, the ancient two and the other two methods, the word, the technical system & The amount of current into each pixel column. 21. The self-illuminating display H 踞 踞 电路 circuit of claim 20, wherein the second processing circuit is based on external image data, and is based on image data of the military 瞀 田 ρ The different processing determines the long-term ritual, and the pixel column describes the processing of the second current amount. 22. The driving circuit of the self-luminous display device of claim 21, wherein the transfer processing is to obtain a current value u' of a maximum value of the image data input from the outside during the first period by the second period. The image data is calculated by calculating an appropriate current value 12, and based on the proportional wrist, sequentially processes the amount of current applied to each of the pixels displayed by the specific image data input during the second period. 23· ^ The driving circuit of the self-luminous display of the request item 2, wherein the first processing circuit has a means for measuring the image data input from the outside, and the measurement result is & The arithmetic processing of the aforementioned second current amount of the pixel column. 24. The driving circuit of the self-luminous display device according to claim 23, wherein the operation processing is performed by using the second current value l3 of the maximum value of the image data from the external input, in the foregoing An actual current is applied between the anode electrode and the cathode electrode to obtain an optimum value. The value is used as the first current value i4, and the ratio i4W is multiplied to the input image 94992-961016.doc 1295792. The processing of the current amount of each pixel is not described based on the specific image data. The driving power of the self-luminous display device according to any one of the items 19 to 24, wherein the driving means for the second processing means for operating only by the first processing means is provided. For the controller of the 26' self-luminous display device, it has the drive circuit of any one of the claims to 24. 27. A self-luminous display device having a driving circuit of any one of w, wherein the self-t-light elements are formed or arranged in a matrix in the pixel row direction and the pixel column direction. shape. The driving method of the display device is characterized in that a current is supplied to the anode electrode portion of the respective light-emitting elements: between the electrodes in the pixel row direction and the image phase direction by forming the self-light-emitting elements of the respective images, so that the foregoing Pixel illumination for driving the display: controlling the amount of current flowing into each of the aforementioned image t columns as a result of the second- or second processing means, the money causing the display portion to emit light; the front (four) = corresponding to the image data input from the outside, Obtaining a first current amount that should flow between the Π and the cathode electrode, and the image of the periphery of the first 彡 image data: a predetermined one-valued processor; the second processing From the externally input image data, the 11⁄4 pole electrode that should be flowed in and the above-mentioned danger ★ Ray second current quantity are according to the aforementioned image 2 - current and the aforementioned image data value of 9492-961016. Doc 1295792 distribution status, preparing a value that suppresses the value of the first current amount by a specific ratio, and the aforementioned suppression ratio is variable according to the distribution of the image data value; and When the current amount corresponding to the white display is expressed by 100, the gradation of the low current region expressed by 30 or less for the specific current amount is a positive number of N1 > 1, N2 > 0 and N1 - N2. The coefficient is set to W, the specific current amount is set to W, the current value at this time is set to Iorg, and the light-emitting period is set to Torg, and the current value is IorgxN1 and the light-emitting period is Torgxl/N2 instead of the current amount. Electricity flow. 94992-961016.doc 1295792 Patent Application No. 093123557 Chinese Graphic Replacement Page (October 1996) 94992-fig-961016.doc 1295792 > 〇93123557 Patent Application Known Article (9) i Replacement Page Chinese Graphic Replacement Page (October 96) / · A Letter 33 S 亮度 Brightness (%) 〇 94992-fig-961016.doc •33- 〇93123557 Patent Application Chinese Graphic Replacement Page (October 96) Month % Daily Repair U Replacement Page 94992-fig-961016.doc •94- 1295792 Patent application No. 093123557 Chinese pattern replacement page (96 years 1 month) No. 101 Vaseng level card raspberry titanium chicken 100 (0/.) 94992-fig-9610l6.doc 1295792 Patent application No. 093123557 Chinese picture replacement page (96 years 1 month) 105 S54 -105- 94992-fig_961016.doc X 1295792 Patent Application No. 093123557 Chinese Graphic Replacement Page (October 1996) 〇 Letter 1 25 邺 Asm%) 94992-fig-9610I6.doc -125- 1295792 Patent Application No. 093123557 Chinese Pattern Replacement Page (October 96) Totsuka: Feiyin Replacement Page 94992-fig-961016.doc 127- 1295792 VII. Designated representative map: (1) The representative representative of the case is: (1). (2) A brief description of the component symbols of this representative diagram: 11a~lid transistor (thin film transistor, TFT) 12 gate driver (gate driver IC circuit) 14 source driver (source driver 1C circuit) 15 EL component ( Light-emitting device) 16 pixels 17a, 17b Gate signal line 18 Source signal line 19 Storage capacitor (additional capacitor, additional capacitor) G Gate S Source D Dip Vdd Current supply line 8. If there is a chemical formula in this case, please disclose The chemical formula that best shows the characteristics of the invention: (none) 94992-961016.doc