玖、發明說明： 【發明所屬之技術領域】 本發明係關於一種全向性波束轉換為不同波柱寬之微波凹透 鏡天線設計方法，特別是指一種將柱狀波轉化為平面波，使該輻 射月匕里集t於某特定需要之方向上，以有效提高最大輻射方向的 方向性係數，而能有效提昇此類天線之指向性之微波凹透鏡天線 設計。 【先前技術】 · 習用傳統基地台天線，其構成上之主要缺點為：基地台所使 用之傳、4天線’其方向性差’天線增益低，為了解決這類天線頻 譜使用效率差，及希望能夠達到360度之全方向性範圍，基地台 通常採用多組約6G度固定之方位角波束寬之陣列天線同時設置。 然基地台所使用陣列天線為線性極化波，經由無數次之多重 路減射，電t皮向量合成後，會出現交疊區某些地方電場強度參 相加而力德幅形成凸起)，某些地方電場強度相減而減弱(振幅 形成凹口）’或完全抵銷，使收訊者受訊接收減弱甚至不良之衰落 (fading )現象。 由此可見’上述習用物品仍有諸多缺失，實非_良善之設計 者，而亟待加以改良。 本案發明人鑑於傳統基地台天線所衍生的各項缺點，乃亟思加 583787 以改良創新，並經多年苦心孤詣潛心研究後，終於成功研發完成 本件全向性波束轉換為不同波柱寬之微波凹透鏡天線設計。 【發明目的】 本發明之目的即在於提供一種全向性波束轉換為不同波柱寬 之微波凹透鏡天線設計方法，係經由本發明可明顯改善傳統基地 台天線衰落及頻譜使用效率差之缺失，更提供多方向性、多波束、 可彈性調整多種不同波束寬選項外，又可免除基地台為了適應不 同需求，需設立多種不同天線之佔地與成本負擔，同時本項發明馨 佔地小、成本低廉更是一特點。 【發明内容】 可達成上述發明目的之全向性波束轉換為不同波柱寬之微波 凹透鏡天線設計方法，包括有一組微波凹透鏡天線21，該微波凹 透鏡天線21係以平面金屬薄板等間距平行排列，即構成波導管之 功用，使電磁場之極化方向和金屬板平行，因而電磁波會以大於參 在真空之相速度'通過’利用此原理設計製作為多組曲率相同、寬 度不同之凹型之金屬板，並將該金屬板係以等間距平行堆疊而 成，使之構成一微波凹透鏡天線21，便可將圓柱電磁波犯轉換為 等相位波前之平面電磁波33。 【實施方式】 8 583787 請參閱圖二，本發明所提供之全向性波束轉換為不同波柱寬 之微波凹透鏡天線設計方法白· τ万沄主要包括有·一組微波凹透鏡天線21， 該天線係為多組曲率相同、寬度不同之凹型金屬板1，該凹型金屬 板1係以等間距¢/平行堆疊而成之_微波凹透鏡天線21。 (一）、原理說明： 輻射電磁波，會因傳播路徑不同之介質而改變傳播之速度， 而該微波凹透鏡天線係以平面金屬薄板，等間距d平行排列，即構成 波導管之功用，當電磁場之極化方向和凹型金屬板1平行時，則 電磁波會以大於在真空之相速度、通過，利用此原理若將設計製作 為曲率相同、寬度不同之凹型金屬板丨（如圖一所示），將若干片凹 型金屬板1以等間距d平行堆疊即構成微波凹透鏡天線21(如圖二 所示），便可將圓柱電磁波32轉換為等相位波前之平面電磁波 33(如圖三所示）。 請參閱圖四，其顯示本發明之凹透鏡設計示意圖，為滿足饋源 31發射之圓柱電磁波，經透鏡後轉換為等相位波前之平面電磁 波’需使沿路徑SAB與沿著路徑SCD有相同之相位延遲，因此 k^(Xf - PC〇s^)= k〇¥-l· ) ( j } 式（1 )可簡化為 /2-1 ^= F ( nCos i9 ~ 1 ^ C 0 \ 按波導理論，電磁波相速、會以大於或等於真空之速度t，通 9 過平行電磁場極化方向之凹型金屬板1，即发明 Description of the invention: [Technical field to which the invention belongs] The present invention relates to a microwave concave lens antenna design method for converting an omnidirectional beam into different wave column widths, in particular, a method for converting a cylindrical wave into a plane wave, so that the radiation month A microwave concave lens antenna design that focuses on the direction of a specific need to effectively improve the directivity coefficient of the maximum radiation direction and effectively improve the directivity of this type of antenna. [Previous technology] · The main disadvantages of conventional base station antennas are: the antenna used by the base station, and the 4 antennas have "bad directivity". The antenna gain is low. In order to solve the poor spectrum efficiency of such antennas, and hope to achieve The 360-degree omnidirectional range, the base station usually uses multiple sets of array antennas with a fixed azimuth beam width of about 6G degrees to set at the same time. However, the array antenna used by the base station is a linearly polarized wave. After multiple times of multipath reduction, the electrical t-skin vectors are synthesized, and the electric field strengths in some places in the overlap area will be added to form a convex pattern.), In some places, the electric field strength is reduced and weakened (the amplitude forms a notch), or it is completely offset, which makes the receiver's receiving reception weakened or even bad fading. It can be seen that there are still many shortcomings in the above-mentioned conventional articles. They are not _ good designers, and need to be improved. In view of the various shortcomings derived from the traditional base station antenna, the inventor of this case desperately added 583787 to improve and innovate. After years of painstaking and meticulous research, he finally successfully developed and completed this omnidirectional beam conversion into a microwave concave lens with different wave column widths. Antenna design. [Objective of the Invention] The purpose of the present invention is to provide a microwave concave lens antenna design method for omnidirectional beam conversion into different wave column widths. The invention can obviously improve the traditional base station antenna fading and the lack of poor spectrum efficiency. Provides multi-directional, multi-beam, and flexible adjustment of a variety of different beam width options, but also eliminates the need for the base station to adapt to the different needs of the establishment of a variety of different antennas and cost burden. At the same time, this invention has a small footprint and cost. Low cost is a feature. [Summary] A microwave concave lens antenna design method for converting the omnidirectional beam into different wave column widths to achieve the above-mentioned object of the invention includes a group of microwave concave lens antennas 21, which are arranged in parallel with a flat metal sheet at equal intervals. That is to constitute the function of the waveguide, so that the polarization direction of the electromagnetic field is parallel to the metal plate, so the electromagnetic wave will be designed to produce multiple sets of concave metal plates with the same curvature and different widths by using this principle at a phase velocity greater than that in the vacuum. The metal plates are stacked in parallel at equal intervals to form a microwave concave lens antenna 21, which can convert cylindrical electromagnetic wave criminals into planar electromagnetic waves 33 of equal phase wavefront. [Embodiment] 8 583787 Please refer to FIG. 2. The design method of microwave concave lens antennas for converting omnidirectional beams to different wave column widths provided by the present invention is white. Τ 10,000 · mainly includes a set of microwave concave lens antennas 21, the antenna It is a plurality of sets of concave metal plates 1 with the same curvature and different widths. The concave metal plates 1 are formed by _ microwave concave lens antenna 21 stacked at equal intervals ¢ / parallel. (1) Explanation of principle: The radiated electromagnetic wave will change the propagation speed due to different media of the propagation path. The microwave concave lens antenna is a flat metal thin plate arranged in parallel at an equal interval d, which constitutes the function of a waveguide. When the polarization direction is parallel to the concave metal plate 1, the electromagnetic waves will pass at a speed higher than that of the vacuum phase. Using this principle, if the design is made into concave metal plates with the same curvature and different widths (see Figure 1), A plurality of concave metal plates 1 are stacked in parallel at an equal interval d to form a microwave concave lens antenna 21 (as shown in FIG. 2), and a cylindrical electromagnetic wave 32 can be converted into a plane electromagnetic wave 33 of an equal phase wavefront (as shown in FIG. 3). . Please refer to FIG. 4, which shows a schematic diagram of a concave lens design according to the present invention. In order to satisfy the cylindrical electromagnetic wave emitted by the feed source 31, the planar electromagnetic wave converted into an equal phase wavefront after passing through the lens needs to have the same characteristics along the path SAB and along the path SCD. Phase delay, so k ^ (Xf-PC〇s ^) = k〇 ¥ -l ·) (j} Equation (1) can be simplified to / 2-1 ^ = F (nCos i9 ~ 1 ^ C 0 \ according to the waveguide In theory, the phase velocity of electromagnetic waves will pass through the concave metal plate 1 parallel to the polarization direction of the electromagnetic field at a speed t greater than or equal to the vacuum, ie,
將依照式（2 )設計之數片凹型金屬板丨，以相等間距平行 堆登擺置，即構成微波凹透鏡天線21，並讓饋源31發送之入射電 場向量平行於凹型金屬板丨，如圖五所示，則輻射電磁波通過這種 透鏡時，其作用有如波導管，則Several concave metal plates designed according to formula (2) are stacked in parallel at equal intervals to form a microwave concave lens antenna 21, and the incident electric field vector sent by the feed 31 is parallel to the concave metal plate 丨 as shown in the figure. As shown in Figure 5, when the radiated electromagnetic wave passes through this lens, it acts like a waveguide.
Id’ (4 ) 整理後得Id ’(4) after finishing
凹型金屬板1間距 適當調整平行凹型金屬板1間距，使符合微波凹透鏡天線 21之/斤射率《幻之條件，則、〉v。，即輻射電磁波於通過金屬時之 相速 比在空氣中為快，故而，此種微波凹透鏡天線21又稱為 加速3L透鏡，利用此種將電磁波加速之特性，可將線性陣列天線 583787 發射之圓柱電磁波32，經過設計適當之曲面構成之加速透鏡天線· 後，轉換為等相位波前之平面電磁波33，如圖三所示。 2一支1,9 GHz之線性陣列天線（同轴共線天線），置放於微 波暗室近場量測系統’配合向量網路分析儀，在距離天線饋源Μ 三倍波長81處，將發射天線對接收天線82左右各三倍波長Μ範 圍内，進行掃描量測，測得線性陣列天線之電場之相位，如圖六. 所示其一久方向位差約為左右，若在發射與接收天線82間，. 擺置預先設計組裝好之微波凹透鏡天線21後，同樣將發射天線對 接收天線82左右各三倍波長81冑圍内，進行掃描量_，所量測 付的平面電磁波3 3前之相位，如圖七所示，相位差約為y左右，_ 幾乎接近符合等相位波前之平面電磁波3 3之條件。 線性陣列天線（同軸共線天線）之圓柱波產生全向性場圖，若 於適當距離處，對圓柱電磁波32截面上加上特殊微波凹透鏡天線 21，即可將圓柱電磁波32轉換為等相位波前之平面電磁波33，經 由改變微波凹透鏡之曲率，改變微波透鏡之面積大小，可調整波 柱之寬窄’微波透鏡面積愈大，波束寬愈窄，指向性愈佳。 (二）、設計步驟·· 一決定折射率w 春 為求凹透鏡之曲率半徑P，需先決定欲組裝之微波凹透鏡天線 21，要採用何種折射率《來設計，首先選擇適合操作頻率之標準天 線，如圖八所示安裝，在距離天線饋源31三倍波長81處，將發 射天線對接收天線82左右各三倍波長81範圍内，進行掃描量測二 測得線性陣列天線之平面電磁波33前之相位，如圖六所示，再將 預先組裝好之數片彼此間距d之平行凹型金屬板1，擺置於天線饋 源31與接收天線82間，如圖九所示，同樣將天線饋源31對接收 天線82左右各三倍波長81範圍内，進行掃描量測，所量測得的 11 583787 平面電磁波前33之相位，如圖七所示以相同之條件量測其相位 經由相位比對求出間距d之平行凹型金屬板1之折射率”，改變兩 平行金屬板1之間距d，即會改變波的折射率《，如 固卞所示為間 距J變化對折射率《之關係圖。 決定半張角沒 微波凹透鏡曲率之半張角ι9，與透鏡之折射率”有相♦關係 由式（2 )得出半張角沒隨折射率《而改變 田 ^ 沒=广…一1[^土 2(1一衫)^/4(1 一《)2 +¾2 — 1 7 4(1-λ)2 +η2 由式（7 )知《< 〇· 6，或 取 《 < 0· 6 由式（7 )得出半張角《9與折射率„之關係曲線（如圖十 之折射率《應採用不同之半張角沒。 > 但因微波凹透鏡之《需^ 因此 不同Pitch of the concave metal plate 1 Adjust the pitch of the parallel concave metal plate 1 appropriately so as to meet the condition of the microwave concave lens antenna 21 / radiation "magic conditions, then,> v. That is, the phase velocity of radiated electromagnetic waves when passing through metal is faster than in air. Therefore, this microwave concave lens antenna 21 is also called an accelerated 3L lens. Using this characteristic of accelerating electromagnetic waves, the linear array antenna 583787 can be emitted. The cylindrical electromagnetic wave 32 is converted into a plane electromagnetic wave 33 with an equal phase wavefront after being designed with an accelerating lens antenna with an appropriate curved surface, as shown in FIG. 3. Two 1,9 GHz linear array antennas (coaxial collinear antennas) are placed in a microwave darkroom near-field measurement system 'with a vector network analyzer, and at a distance of 81 times the wavelength M of the antenna, the The transmitting antenna scans the receiving antenna 82 in the range of three times the wavelength M, and measures the phase of the electric field of the linear array antenna, as shown in Fig. 6. The one-time direction position difference is about left and right. Between the antennas 82, after the microwave concave lens antenna 21 designed and assembled in advance is arranged, the transmitting antenna is also scanned around the receiving antenna 82 at three times the wavelength of 81 左右, and the measured planar electromagnetic wave is measured. 3 3 The previous phase, as shown in Fig. 7, has a phase difference of about y, and _ is almost close to the condition of a plane electromagnetic wave 33 which is equal to the phase wavefront. The cylindrical wave of a linear array antenna (coaxial collinear antenna) generates an omni-directional field pattern. If a special microwave concave lens antenna 21 is added to the cross section of the cylindrical electromagnetic wave 32 at an appropriate distance, the cylindrical electromagnetic wave 32 can be converted into an equal phase wave. The front planar electromagnetic wave 33 can be adjusted by changing the curvature of the microwave concave lens and changing the area of the microwave lens. The larger the width of the wave column, the larger the microwave lens area, the narrower the beam width, and the better the directivity. (II) Design steps ... Determine the refractive index w To determine the curvature radius P of the concave lens, first determine the refractive index of the microwave concave lens antenna 21 to be assembled. To design, first select the standard suitable for the operating frequency. The antenna is installed as shown in Fig. 8. At a distance of three times the wavelength 81 from the antenna feed 31, the transmitting antenna is paired with the receiving antenna 82 and the three times the wavelength 81 respectively. Scanning and measuring are performed. For the phase before 33, as shown in Fig. 6, a number of pre-assembled parallel concave metal plates 1 with a distance of d from each other are placed between the antenna feed 31 and the receiving antenna 82, as shown in Fig. 9. The antenna feed 31 performs a scanning measurement on the range of three times the wavelength 81 of the left and right of the receiving antenna 82. The measured phase of the 11 583787 plane electromagnetic wavefront 33 is measured under the same conditions as shown in Figure 7. Phase comparison finds the refractive index of the parallel concave metal plate 1 with a distance d. Changing the distance d between the two parallel metal plates 1 will change the refractive index of the wave. Key point Figure. The half-opening angle ι9, which determines the curvature of the microwave concave lens and the half-opening angle, has a relationship with the refractive index of the lens. The relationship between the half-opening angle and the refractive index "is not obtained by Equation (2). Soil 2 (1 one shirt) ^ / 4 (1 one <<) 2 + ¾2 — 1 7 4 (1-λ) 2 + η2 From the formula (7), we know that < 0 · 6, or take < 0 · 6 The relationship between the half-opening angle "9 and the refractive index" is obtained from the formula (7) (as shown in the refractive index of Fig. 10, a different half-opening angle should be used. ≫
三決定焦距F 以傳統基地台線性陣列天線（同軸共線天線）之長度， 計微波凹透鏡透鏡焦距F之參考。 P局汉 四微波凹透鏡曲率之設計 依照工作波長選擇適當之焦距F、折射率"及半張角5，Third, the focal length F is determined by the length of the traditional base station linear array antenna (coaxial collinear antenna), and the reference of the focal length F of the microwave concave lens. P Bureau Han The design of the curvature of the four microwave concave lenses According to the working wavelength, the appropriate focal length F, refractive index "
式（2 )設計微波凹透鏡之曲率半徑。 1之用 五決定微波凹透鏡天線21堆疊之高度D 、，為使同軸共線天線輻射之圓柱電磁波32，能^全確 平面電磁波3 3，微波凹透鏡天绩9 j > 逍鏡天線21之尚度D,應設計與發射用之 583787 同軸共線天線等高度，不同之折射率„及半張ρ，所設計出 波凹透鏡天線21堆疊之高度D，亦隨之改變。 六組裝發射天線與微波凹透鏡天線21 將發射天線置於設計堆疊完成之微波凹透鏡天線21之焦點， 如圖十二所示，即組成將圓柱電磁波32轉換為平面電磁波⑽之 二維平面結構。 將輻射圓柱電磁波之全向性同軸共線天線，置放於不同曲率 微波透鏡天線21之對應焦距F處，即可產生不同指向性之等相位 波前之平面電磁波33，如圖十三所示。 若將多組不同折射率《，不同半張角沒，不同焦距F，所設計 之微波凹透鏡組裝如圖十四、十五所示，即為多波數多指向性之 特殊微波凹透鏡天線。 【特點及功效】 本發明所提供之全向性波束轉換為不同波柱寬之微波凹透鏡 天線21設計，與前述引證案及其他習用技術相互比較時，更具有 下列之優點： (1)本發明之微波凹透鏡天線21可明顯改善傳統基地台天線 衰落及頻譜使用效率差之缺失，更提供多方向性、多波束、可彈 性調整多種不同波束寬選項外，又可免除基地台為了適應不同需 求，需設立多種不同天線之佔地與成本負擔。 上列詳細說明係針對本發明之一可行實施例之具體說明，惟該 實施例並非用以限制本發明之專利範圍，凡未脫離本發明技藝精 13 583787 神所為之等效實施或變更，均應包含於本案之專利範圍中。 綜上所述，本案不但在技術思想上確屬創新，並能較習用物品 增進上述多項功效，應已充分符合新穎性及進步性之法定發明專 利要件’爰依法提出申請，懇請貴局核准本件發明專利申請案， 以勵發明，至感德便。 【圖式簡單說明】 請參閱以下有關本發明一較佳實施例之詳細說明及其附圖， 將可進一步瞭解本發明之技術内容及其目的功效；有關該實施例 之附圖為： 圖一為本發明全向性波束轉換為不同波柱寬之微波凹透鏡天 線21所設計之凹型金屬板之側視圖； 圖二為本發明之微波凹透鏡天線21之立體側視圖； 圖二為本發明之圓柱電磁波32經微波凹透鏡天線21轉換為 等相位波前平面電磁波33之示意圖； 圖四為本發明之凹透鏡設計示意圖； 圖五為本發明之電磁場與微波凹透鏡天線21之極化關係立體 圖； 圖六為本發明之圓柱電磁波量測之相位圖； 圖七為本發明之圓柱電磁波32經微波凹透鏡天線21轉換後 置測之等相位波前平面電磁波3 3之相位圖； 14 583787 圖八為本發明量測未加金屬平板之相位圖示； 圖九為本發明量測間距為d堆疊之平行金屬板之相位圖示； 圖十為本發明之微波凹透鏡天線21其金屬平板間距與折射率 之關係曲線圖； 圖十一為本發明之半張角與折射率之關係曲線圖； 圖十二為本發明之同轴共線天線與微波凹透鏡天線21之配置 圖； 圖十三為本發明之不同曲率之微波凹透鏡天線21對應不同之 焦距產生不同指向性波束圖示； 圖十四為本發明之多波束多指向性之微波凹透鏡天線21頂視 圖；以及 圖十五為本發明之微波凹透鏡天線21實作照相圖。 【主要部分代表符號】 户焦點至透鏡曲面任意點之距離 w折射率 «9半張角 F焦距 ，電磁波相速 νσ真空之速度 ¢/間距 D局度 1凹型金屬板 21微波凹透鏡天線 15 583787 22凹型之金屬板之間距 23凹型透鏡天線的高度 31同軸共線天線饋源 32圓柱電磁波 3 3等相位波前平面波 41焦點至透鏡曲面任意點的的距離 42半張角 43焦距 81三倍波長 82接收天線 _ 91同軸共線天線饋源和接收天線的距離 92平行金屬板的寬度 93間距為d堆疊之平行金屬板 141第1組微波凹透鏡天線 142第2組微波凹透鏡天線 143第3組微波凹透鏡天線 144第4組微波凹透鏡天線 145第5組微波凹透鏡天線 146第6組微波凹透鏡天線 ® 1422第1組微波凹透鏡天線的焦距 1462第6組微波凹透鏡天線的焦距 1411第1組微波凹透鏡天線的輻射場圖 1421第2組微波凹透鏡天線的輻射場圖 1431第3組微波凹透鏡天線的輻射場圖 1441第4組微波凹透鏡天線的輻射場圖 145 1第5組微波凹透鏡天線的輻射場圖 1461第6組微波凹透鏡天線的輻射場圖 16The formula (2) designs the radius of curvature of the microwave concave lens. 1 is used to determine the stacking height D of the microwave concave lens antenna 21, in order to make the cylindrical electromagnetic wave 32 radiated by the coaxial collinear antenna, it can ^ fully confirm the planar electromagnetic wave 3 3, the microwave concave lens is a good thing 9 j > The degree D should be designed and transmitted at the same height as the 583787 coaxial collinear antenna, with different refractive indexes and half-sheet ρ. The height D of the wave-concave lens antenna 21 stacked is also changed. Six assembly of transmitting antennas and microwaves Concave lens antenna 21 Place the transmitting antenna at the focal point of the microwave concave lens antenna 21 that has been designed and stacked, as shown in Figure 12, which constitutes a two-dimensional planar structure that converts cylindrical electromagnetic waves 32 into planar electromagnetic waves. Omnidirectional radiation of cylindrical electromagnetic waves The coaxial coaxial collinear antenna is placed at the corresponding focal length F of the microwave lens antenna 21 with different curvatures, and plane electromagnetic waves 33 of equal phase wavefronts with different directivity can be generated, as shown in Figure 13. If multiple groups of different refraction are used, Rate ", different half-opening angles, different focal lengths F, the design of the microwave concave lens assembly shown in Figures 14 and 15, which is a multi-wavelength multi-directional special microwave concave lens [Features and effects] The design of the microwave concave lens antenna 21 with omnidirectional beam conversion provided by the present invention with different wave column widths has the following advantages when compared with the aforementioned citations and other conventional technologies: (1) The microwave concave lens antenna 21 of the present invention can obviously improve the traditional base station antenna fading and the lack of poor spectrum utilization efficiency. It also provides multi-directionality, multi-beam, and can flexibly adjust a variety of different beam width options. It can also eliminate the need for the base station to adapt to different Requirements, the land occupation and cost burden of multiple different antennas need to be set up. The above detailed description is a specific description of one of the feasible embodiments of the present invention, but this embodiment is not intended to limit the scope of the patent of the present invention. Skilled art 13 583787 Equivalent implementations or changes by God should be included in the scope of patents in this case. In summary, this case is not only technically innovative, but also can improve the above-mentioned multiple effects over conventional items. The statutory invention patent elements that are fully in line with novelty and progress are 'applied in accordance with the law, and your office is kindly requested to approve this [Application for invention patents to encourage inventions, to the utmost convenience] [Brief Description of the Drawings] Please refer to the following detailed description of a preferred embodiment of the present invention and the accompanying drawings, which will further understand the technical content of the present invention and its Purpose effect; The drawings related to this embodiment are: FIG. 1 is a side view of a concave metal plate designed by the microwave concave lens antenna 21 in which the omnidirectional beam is converted into different wave column widths of the present invention; FIG. 2 is a microwave concave lens of the present invention A perspective side view of the antenna 21; FIG. 2 is a schematic diagram of the cylindrical electromagnetic wave 32 of the present invention converted into an equi-phase wavefront planar electromagnetic wave 33 by the microwave concave lens antenna 21; FIG. 4 is a schematic diagram of the concave lens design of the present invention; FIG. 5 is an electromagnetic field of the present invention A perspective view of the polarization relationship with the microwave concave lens antenna 21; Figure 6 is a phase diagram of the cylindrical electromagnetic wave measurement of the present invention; Phase diagram of 3 3; 14 583787 Figure 8 is a phase diagram of the measurement without a metal plate in the present invention; Figure 9 is a measurement chamber of the present invention Phase diagram of parallel metal plates stacked by d; Figure 10 is a graph showing the relationship between the metal plate spacing and the refractive index of the microwave concave lens antenna 21 of the present invention; Figure 11 is a graph showing the relationship between the half-opening angle and the refractive index of the present invention ; Figure 12 is a configuration diagram of the coaxial collinear antenna and the microwave concave lens antenna 21 of the present invention; Figure 13 is a diagram of the microwave concave lens antenna 21 with different curvatures according to the present invention to generate different directional beams corresponding to different focal lengths; Figure 10 4 is a top view of the multi-beam and multi-directional microwave concave lens antenna 21 of the present invention; and FIG. 15 is a photographic view of the microwave concave lens antenna 21 of the present invention. [Representative symbols of main parts] The distance from the focal point of the user to any point on the lens surface w index of refraction «9 half-opening angle F focal length, electromagnetic wave phase velocity νσ vacuum speed ¢ / pitch D locality 1 concave metal plate 21 microwave concave lens antenna 15 583787 22 concave The height of the metal plate from the 23 concave lens antenna 31 Coaxial collinear antenna feed 32 Cylindrical electromagnetic wave 3 3 Equal phase wavefront plane wave 41 The distance from the focal point to any point on the lens surface 42 Half angle 43 Focal length 81 Three times the wavelength 82 Receiving antenna _ 91 The distance between the coaxial collinear antenna feed and receiving antennas 92 The width of the parallel metal plates 93 The parallel metal plates with a distance of d stacked 141 The first group of microwave concave lens antennas 142 The second group of microwave concave lens antennas 143 The third group of microwave concave lens antennas 144 Group 4 Microwave Concave Lens Antenna 145 Group 5 Microwave Concave Lens Antenna 146 Group 6 Microwave Concave Lens Antenna® 1422 Group 1 Microwave Concave Lens Antenna Focal Length 1462 Group 6 Microwave Concave Lens Antenna Focal Length 1411 Group 1 Microwave Concave Lens Antenna Radiation Field Diagram 1421 Radiation field of the second group of microwave concave lens antennas 1431 Radiation field of the third group of microwave concave lens antennas 1441 Group 4 microwave Radiation field diagram of concave lens antenna 145 1 Radiation field diagram of group 5 microwave concave lens antenna 1461 Radiation field diagram of group 6 microwave concave lens antenna 16