A6 B6 經濟部中央標準局員工消費合作社印製 五、發明説明（1 ) 發明背軎 本發明掲示一種換流器裝置，其中換流器禽頻輸出部 份造成回饋到整流器，而高頻電流供應到整流器大致上 可能在AC電源電壓之整個範圔實施，以便改善輸入功因 〇 相SS持術說Bfl 對習用換流器裝置經建議用於改善輸入功因及效率， 例如，已經在M.前原（Maehara)氏之日本專利公開發行 第4 - 1 9 3 0 6 7號中證明一種換流器裝置，其己經用做為放 電燈起動裝置。更明確地，該放電燈起動裝置包含橋式 二極體做為AC電源電壓之整流器、平流電容器 (Smoothing capacitor)用來使橋式二極體輸出平流、 換流器電路包括振盪糸統且轉換跨於平流電容器之電壓 成為髙頻電壓做為輸出、及輸入功因改善電路，其造成 換流器高頻输出部份，經至少多加電容器（further capacitor)做為阻抗元件，反饋到橋式二極體，且大致 在AC電源電壓整個範圍實施高頻電流供應到橋式二極體 〇 本換流器裝置之換流器電路中，一對交換元件成串聯 連接到平流電容之兩端，放電燈跨接在具有直流（DC)成 分削除電容器（cutting capacitor)及電感器間置之交 換元件對之一上，而用於放電燈燈絲之預熱電容器跨接 在燈絲之非電源（non-source)側端。本情形中，預熱電 -3 - -------------»1— ---------裝------.玎-----^ (請先閲讀背面之注意事項再填寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4规格（210 X 297父釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 B6_ 五、發明説明（2 ) 容以及電感器構成包含在換流器電路之振盪条統》 在上述換流器電路中，跨接在平流電容器之電壓，以 交換元件對之交變高頻開啓及開閉來轉換成高頻電壓， 是為了放電燈之高頻起動之目的。卽，當交換元件對之 第1對開啓時，放電燈經過此種高頻起動，高頻電壓經 平流電容器、第1交換元件、電感器及DC成分削除電容 器，來供應到放電燈，而當交換元件第2對在上述電源 供應期間，以DC成分削除電容器内所累積電荷做為電源 來開啓時，電源在第1交換元件經DC成分削除電容器、 電威器及第2交換元件而一開啓，卽在相反方向供應到 放電燈。 上述放電燈起動裝置之輸入功因改善電路中，電路包 含電容器做為阻抗元件，連接在DC成分削除電容器對放 電燈之接合點、及橋式二極體之正極側輸出端之間，而 二極體連接在橋式二極體正極侧輸出端及平流電容器之 間I放電燈装置中，包括該輸入功因改善電路，當交換 元件對之第2對開啓時，造成電流流經橋式二極體、電 容器做為阻抗元件、DC成分削除電容器、電感器及第2 交換元件之路線，且進一步因為包含電容器做為阻抗元件 及電威器之振盪糸統之作用，在交換元件對之第1對開 啓狀況期間，造成換流電流流經主要電容器做為阻抗元 件、功因改善電二極體、交換元件對之第1對、電威器 及DC成分削除電容器之路線。 -4 - (請先閲讀〃背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297公坌） 82. 5. 20,000 A6 B6 經濟部中央標準局員工消費合作社印製 五、發明説明（3 ) 如此，輸入功因能在AC電源電壓之整値範圍，以高頻 供應電流經做為阻抗之電容器到橋式二極體來改善，而 因而，輸入功因改善能以增加阻抗用電容器及二棰體之 此種簡單方法來實施》 然而，上述習用換流器裝置所使用為放電燈起動裝置 中，一經振盪即有漣波成分在交換元件對之交換頻率中 産生，變成顯著之此種問題發生，在此種諸如放電燈之 負載作業上産生不良影湛，其狀況可能在放電燈之光输 出中，發生閃爍或類似情形。 發明概沭 因而，本發明之目的在提供一種換流器裝置，其能克 服習用技術之上述問題，且尤其，顯箸降低在裝置負載 上造成不良影饗之漣波成分，其輸入功因要以造成高頻 輸出部反饋到用於AC電源電壓之整流器來改善，並大致 在A C電源電壓整個範圍得到高頻電流供應到整流器。 根據本發明，上述目的能以換流器來實現，其中AC電 源電壓經整流器整流，其整流輸出經平流電容器而平流 ，跨接在平流電容器之電壓，經包括第1振盪条統之換 流器電路轉換成高頻電壓，輸入功因改善電路造成換流 器電路高頻輸出部份，經阻抗元件反饋到整流器之整流 輸出端，而大致在AC電源電壓整個範圍實施高頻電流供 應到整流器，而換流器電路中並連接到整流器之整流輸 出端之阻抗元件，構成至少第1振盪条統及第2振盪条 ------------------------裝------#---->^ (請先閲讀背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297 Uf) 82. 5. 20,000A6 B6 Printed by the Consumer Cooperative of the Central Standards Bureau of the Ministry of Economic Affairs 5. Description of the invention (1) Invention The present invention shows a converter device in which the bird's frequency output part of the converter causes feedback to the rectifier and high-frequency current is supplied The rectifier may be implemented in the entire range of the AC power supply voltage in order to improve the input power factor. The phase SS holding technique Bfl is recommended to improve the input power factor and efficiency of conventional converter devices. For example, it has been used in M. Japanese Patent Laid-Open Publication No. 4-193 0 6 7 of Maehara proves a converter device which has been used as a discharge lamp starting device. More specifically, the discharge lamp starting device includes a bridge diode as a rectifier for the AC power voltage, and a smoothing capacitor for smoothing the output of the bridge diode. The inverter circuit includes an oscillation system and converts The voltage across the smoothing capacitor becomes the high-frequency voltage as the output and the input power factor improvement circuit, which causes the high-frequency output part of the converter to be fed back to the bridge type 2 through at least a further capacitor as an impedance element. A high-frequency current is supplied to the bridge diode in the entire range of the AC power supply voltage. In the inverter circuit of the inverter device, a pair of exchange elements are connected in series to both ends of the smoothing capacitor and discharge. The lamp bridge is connected to one of the exchange element pairs having a direct current (DC) cutting capacitor and an inductor, and the preheating capacitor for the discharge lamp filament is bridged to the non-source of the filament. ) Side end. In this case, the preheating power -3-------------- »1— --------- installation ------. 玎 ----- ^ (Please read the precautions on the back before filling this page) This paper size is applicable to China National Standard (CNS) A4 specification (210 X 297 father) 82. 5. 20,000 printed by A6 B6_ V. Description of the invention (2) The capacitor and the inductor structure are included in the oscillation circuit of the inverter circuit. In the above inverter circuit, the voltage across the smoothing capacitor is switched on, and the switching element is switched on to the high frequency and Opening and closing to convert to high-frequency voltage is for the purpose of high-frequency starting of the discharge lamp. Alas, when the first pair of switching element pairs is turned on, the discharge lamp starts through such high frequency, and the high frequency voltage is supplied to the discharge lamp through the smoothing capacitor, the first switching element, the inductor, and the DC component removal capacitor, and when When the second pair of switching elements is turned on during the above-mentioned power supply period, using the electric charge accumulated in the DC component removal capacitor as the power source, the power is turned on at the first switching element after the DC component is removed from the capacitor, the electric device, and the second switching element.卽 is supplied to the discharge lamp in the opposite direction. In the input power factor improving circuit of the above-mentioned discharge lamp starting device, the circuit includes a capacitor as an impedance element, which is connected between the junction point of the DC component removal capacitor to the discharge lamp and the positive-side output terminal of the bridge diode, and The pole body is connected between the output terminal of the positive side of the bridge diode and the smoothing capacitor. The discharge lamp device includes the input power factor improving circuit. When the second pair of the switching element pair is turned on, the current flows through the bridge type two. The pole body and capacitor are used as the impedance element, the DC component removes the capacitor, the inductor, and the second switching element. Furthermore, because the capacitor includes the capacitor as the oscillation system of the impedance element and the electric device, it is the first component of the switching element pair. During the pair-on condition, the route that causes the commutation current to flow through the main capacitor as the impedance element, the power factor improving electric diode, the first pair of the switching element pair, the electric power device, and the DC component removal capacitor. -4-(Please read the notes on the back of the page before writing this page) This paper size is applicable to China National Standard (CNS) A4 specification (210 X 297) 坌 82. 5. 20,000 A6 B6 Central Bureau of Standards, Ministry of Economic Affairs Printed by the employee consumer cooperative V. Invention description (3) In this way, the input power factor can be improved within the entire range of the AC power voltage, and the high-frequency supply current is improved through the capacitor as an impedance to the bridge diode, and therefore, The improvement of the input work factor can be implemented by such a simple method of increasing the impedance with a capacitor and a two-body body. However, in the above-mentioned conventional converter device used as a discharge lamp starting device, once oscillating, there is a ripple component in the exchange element pair. This problem occurs in the switching frequency, and it becomes a significant problem. In such a load operation as a discharge lamp, a bad image is generated. The condition may be flickering or the like in the light output of the discharge lamp. SUMMARY OF THE INVENTION Therefore, the object of the present invention is to provide a converter device which can overcome the above-mentioned problems of conventional technology, and in particular, significantly reduces the ripple component that causes bad effects on the device load, and the input power factor It is improved by causing the high-frequency output section to feed back to the rectifier for the AC power supply voltage, and the high-frequency current is supplied to the rectifier approximately in the entire range of the AC power supply voltage. According to the present invention, the above-mentioned object can be achieved by a converter, wherein the AC power voltage is rectified by a rectifier, and its rectified output is smoothed by a smoothing capacitor, and the voltage across the smoothing capacitor is passed through the converter including the first oscillation system. The circuit is converted into a high-frequency voltage. The input power is caused by the improvement circuit to cause the high-frequency output part of the inverter circuit, which is fed back to the rectifier output terminal of the rectifier via an impedance element. The impedance element in the converter circuit and connected to the rectifier output of the rectifier constitutes at least the first oscillation bar and the second oscillation bar -------------------- ---- 装 ------ # ---- > ^ (Please read the notes on the back before copying this page) This paper size is applicable to China National Standard (CNS) A4 specification (210 X 297 Uf) 82. 5. 20,000
I A6 B6 0 Μ 及 1 第 之 率 頻 定 固 有 具 以 路 I 9η 器 流 Μ換 <中 J其 説 月 ， 發份 、部 五统 負 到 出 輸 應 供 所 得 使 其 業 作 來 置 裝 制 0 控等 之相 中常 統恆 条致 纆大 振載 示 所 圖 附 照 參 細 〇 詳頴 明明 發得 本變 在將 ， ， 點明 優說 及之 的中 目文 他下 其在 明而 發例 本施 實 明 說 菫 圖 路 之 例 施 實 .， 置圖 裝形 器波 流之 換業 明作 發路 本電 據 稂圖 是是 示示 J所所 ^12I玉目_ 圖 是 4 及 3 ·， 圖圖 路 電 明 説 之 態 模 業 作 同 不 互 相 之 例 施 實 rH 1 盪 振 値 兩 中 路 S ^ΒΓ 1 圖 在 生 發 態 模 業 作 ； 同圖 不性 關待 有之 是面 5 方 圖统 条 統 条 盪 振 値 兩 中 路 ΙΑ 圖 在 生 發 明 說 於 用 是 7 ·， 及圖 6 路 圖電 之 輸 之 路 Be ΐρκ 器 流 換 括 包 所 中 壓 i SR 源 I 對 置 裝 1 圖 是 δ •’ 圖圖 出 路 電 之 例 ;施 圖實 形一 波另 明置 説裝 之器 圖流 出換 輸明 8 發 圖本 到據 得根 於是 用示 是所 ο 9 1 圖圖 (請先閱讀背面之注意事項再塡寫本頁) 圖 經濟部中央標準局員工消費合作社印製 至圖 1 3 1 1 雜 圖及圖電 ; 之 圖 性 特 出 輸 同 不 之 出 輸 流 整 中 路 電 ο il 圖 對 是 2 及 列 施 實 他 其 之 置 裝 器 流 換 明 發 本 據 根 為 示 所 本紙張尺度適用中國國家標準（CNS)甲4规烙（210 X 297公釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 __B6_ 五、發明説明（5 ) 在此必需理解，雖然本發明將參照附圖所示實施例加 以説明，但本作法不限制本發明僅在這些實施例，而是 仍包括可能所有變更、修正及等效布置在發明之申請專 利範圍之範轉内。 窗掄例：>_紬説Bfl 在此參照圖1,在電路中所示為根據本發明換流器裝 置之實施例，且首先將參照根據本發明所要降低漣波成 分之發生，以促進更加了解本發明。裝置包含換流器電 路11，而電容器C4其連接做為阻抗元件，當電流自橋式 二極體DB流經電容器C4、DC成分削除電容器C3、電烕器 L1及一對交換元件Q1及Q2之第2個Q2之路線時，將以圖 1所示箭頭方向充電，類似上述習用裝置之方式另一 方面，電容器C4在電流主要流經電容器C4、二極體D3、 該對交換元件之第1個Q1、電烕器L1及電容器C3之路線 實施放電，一經放電，卽造成跨接在電容器C4之電壓降 低。 轚容器C4之充電及放電，不是在交換元件Q1及Q2對之 開啓及關閉相同時序進行，而是以電壓值對跨接電容器 C 4之電壓Ve4、電源電壓Vin、跨接電感器L 1之電壓 及跨接電容器C3之電壓Ve3之鼸僳來決定、即，以圖3 及4所示兩者間之切換作業狀況，對此電源電壓V in之 裝置輸出，·如圖2波形（a)所示，造成輸出包線波形變 動，如圖2波形（b)至（d)之點線所示。在圖2波形（b) (請先閱讀背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297公釐） 82. 5. 20,000 A6 B6 經濟部中央標準局員工消費合作社印製 五、發明説明（6 ) 及（d)所示此種狀況中，尤其，包線波形之最大及最小 值間之差，或換言之，漣波成分變得顯箸。現在考慮一 種情形，其中第2交換元件Q2開啓，出現有兩種模態， 其中之一是第1振盪条統，如圖3中點線所示，其電流 流經雷容器C3、諧振電烕器L1、第2交換元件Q2、諧振 電容器C2及諸如放電燈之負載La之路線，而其另一是第 2振盪条統，如圖4點線所示，對其增加自橋式二極體 DB、電容器C4、電容器C3、電威器L1及第2交換元件Q2 之路線，而電路作業在交換元件對之各開啓循環内之這 兩種模態間切換，同時切換時序亦以AC週期中電源電壓 Vin之大小而變動β圖4所示第2振盪糸統，經橋式二 極體DB連接到電源，以致隨電源電壓Vin變較大，第2交 換元件Q2切換到該第2振盪糸統之各周期期間延長，而 整锢電路布置造成受第2振盪条統嚴重影響。 另一方面，當在第1及第2振盪条統方面獨立地得到 負載電流iLa待性時，其將如圖5所示β該第1及第2振 盪条統之負載電流待性，分別以圖5中1及2線表示。 在此，第1振盪条統獨立地如圖6所示，同時第2振盪 条統如圖7所示。如圖5所見，判斷其中負載電流ila 之漣波成分，如圖2波形（c)為最小之頻率f,是在兩個 振盪糸統特性大致相同狀況下。意即，在f1=f2狀況 下，其中在第1振盪条統中之ila大於在第2振盪条統 之ila，負載電流ila當電流電壓Vin變較大時深受第2振 丨裝------.玎-----^ (請先閲讀背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297公釐） 82. 5. 20,000I A6 B6 0 Μ and the first rate of the frequency is inherently fixed with the path I 9η device flow M for < Zhong J Qi said month, the distribution, the Ministry of the five responsibilities to the output should be provided for the income to make it installed. In the system of control and control, the Changtong Confidence Article issued a message to Dazhen. The attached picture is detailed. The details were clearly issued. This example shows the implementation of the map. This is the example of the layout of the wave of the shaper. The map is issued by the institute. ^ 12I 玉 目 _ Picture is 4 and 3. ·, The example of Tutu Road's state-of-the-art model is different from each other. The implementation of rH 1 oscillates the two middle paths S ^ ΒΓ 1 The square chart system is oscillating and vibrates the two middle roads IA. Figure 3 shows that the invention uses 7 ·, and Figure 6 shows the power transmission path of the Be ΐρκ device, including the medium-voltage i SR source I pair. Fig. 1 is an example of δ • 'diagram output circuit; The figure of the installed equipment was changed out and replaced with the output of the output. 8 The printed version is based on the instructions. 9 1 Figure (please read the precautions on the back before writing this page) Figure Central Standard of the Ministry of Economy Printed by the Consumer Cooperative of the Bureau to Figure 1 3 1 1 Miscellaneous maps and pictures; Figures are specific to the output, the output is not the same as the current in the middle of the road, and the picture pair is 2 and the column implements other device flows. Reprinting and issuing this document is based on the indication that the paper size is applicable to the Chinese National Standard (CNS) A4 regulations (210 X 297 mm) 82. 5. 20,000 A6 printed by the Consumer Cooperative of the Central Standards Bureau of the Ministry of Economic Affairs __B6_ V. Invention Explanation (5) It must be understood here that although the present invention will be described with reference to the embodiments shown in the drawings, this method does not limit the present invention to only these embodiments, but still includes all possible changes, modifications and equivalent arrangements. Within the scope of the patent application scope of the invention. Window example: > _ Say Bfl Here, referring to FIG. 1, an embodiment of a converter device according to the present invention is shown in the circuit, and firstly, the occurrence of ripple components to be reduced according to the present invention will be referred to in order to promote Learn more about the present invention. The device includes an inverter circuit 11, and the capacitor C4 is connected as an impedance element. When a current flows from the bridge diode DB through the capacitor C4, the DC component removes the capacitor C3, the capacitor L1, and a pair of exchange elements Q1 and Q2. The second Q2 route will be charged in the direction of the arrow shown in Figure 1, similar to the conventional device. On the other hand, the capacitor C4 mainly flows through the capacitor C4, the diode D3, and the first pair of switching elements. One Q1, the circuit of capacitor L1 and capacitor C3 are discharged. Once discharged, the voltage across capacitor C4 is reduced.轚 The charging and discharging of the container C4 is not performed at the same timing as when the switching elements Q1 and Q2 are turned on and off. Instead, the voltage Ve4, the power supply voltage Vin, and the jumper inductor L1 are connected to each other by the voltage value. The voltage and the voltage Ve3 of the jumper capacitor C3 are determined, that is, according to the switching operation conditions shown in Figs. 3 and 4, the device output of this power supply voltage V in is shown in Fig. 2 (a) As shown, the waveform of the output envelope changes, as shown by the dotted lines in the waveforms (b) to (d) of FIG. 2. Waveform (b) in Figure 2 (Please read the notes on the back before copying this page) This paper size applies to China National Standard (CNS) A4 specification (210 X 297 mm) 82. 5. 20,000 A6 B6 Ministry of Economic Affairs Printed by the Consumer Standards Cooperative of the Central Bureau of Standards 5. In the situation shown in the invention description (6) and (d), in particular, the difference between the maximum and minimum values of the envelope waveform, or in other words, the ripple component becomes significant. . Now consider a situation in which the second switching element Q2 is turned on and two modes appear. One of them is the first oscillating system. As shown by the dotted line in FIG. 3, its current flows through the lightning vessel C3 and the resonance circuit. L1, the second switching element Q2, the resonant capacitor C2, and the load La such as a discharge lamp, and the other is the second oscillation system, as shown by the dotted line in FIG. 4, adding a self-bridge diode The route of DB, capacitor C4, capacitor C3, power amplifier L1 and second switching element Q2, and the circuit operation is switched between these two modes in each switching cycle of the switching element pair, and the switching timing is also in the AC cycle The magnitude of the power supply voltage Vin varies. The second oscillation system shown in FIG. 4 is connected to the power supply via the bridge diode DB, so that as the power supply voltage Vin becomes larger, the second switching element Q2 switches to the second oscillation. The period of each cycle of the system is prolonged, and the whole circuit layout is seriously affected by the second oscillation system. On the other hand, when the load current iLa standby is obtained independently in terms of the first and second oscillating systems, it will be β as shown in FIG. 5 the load current standby of the first and second oscillating systems. Lines 1 and 2 are shown in FIG. 5. Here, the first oscillating system is independently shown in FIG. 6, and the second oscillating system is shown in FIG. 7. As shown in Fig. 5, the ripple component of the load current ila is judged. As shown in Fig. 2, waveform (c) is the minimum frequency f, under the condition that the characteristics of the two oscillation systems are about the same. In other words, under the condition of f1 = f2, where ila in the first oscillating system is larger than ila in the second oscillating system, the load current ila is deeply affected by the second vibration when the current voltage Vin becomes larger-- ----. 玎 ----- ^ (Please read the precautions on the back before writing this page) This paper size is applicable to China National Standard (CNS) A4 (210 X 297 mm) 82. 5. 20,000
I 經濟部中央標準局員工消費合作社印製 A6 __B6_ 五、發明説明（7 ) 盪条統影響，且當電流電壓V.為大時，負載電流i1a變 m la 得較小，如圖2 (d)所示β當f = f1，其中第1振盪条統 之ila小於第2振盪条統之ila時，相反地，負載電流 ila當電源電壓Vin增加時，會增加如圖2 ( b )波形所示 。因而，負載電流ila之漣波成分變成最小之狀況可視 為f = f〇 ,其中第1振盪条統之ila大致等於第2振盪条 統之ila。 因為本情形中，一痼直接有助於漣波成發生，是電源 電壓vin之電源電壓vin，輸出特性（實際上，電源電壓 Vin2絶對值丨Vin I ,因為窜源電壓經橋式二掻體供應 到其下一级電路，且已經得到換流器装置，其如圖8所 示，其中輸出（例如，跨於負載之電壓）置於縱座標上 ,同時電源電壓之絶對值置於横座標。圖示中，値別絶 對值值是瞬間值，且亦表示電源電壓之最大值V P更明 確地，當圖1之換流器裝置中，電源電壓之絶對值 I V in I及輸出電壓如圖9所示此種狀況時，在 I V in I = 0下之输出V 可得自在t = ’之前及後之微 短時間At期間之值，在丨| =VP下之輸出V &亦可 in out 得自在t = t3 '之前及後之撤短時間At期間，且同樣地 ，在任意I vin I下之輸出，可得自在I vin |到達 (例如，t = t 2 )時間之前及後之撤短時間△ t之值。在 此，微短時間At必需最佳地設定數倍大如換流器電路 中所使用之交換元件頻率，使任何丨vini變動成為可 -9- (請先閱讀背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297公筮） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 _B6_ 五、發明説明（8 ) 忽略之位準。 如自圖8顯然可見，當換流器電路11之振盪頻率成為 f = f〇 '時，輸出大致成為常數，且漣波成分能夠降低。 根據本發明圖1實施例中，提供有控制裝置11a,使得 換流器電路11在兩値振盪条統之输出將大致相互相等之 頻率f〇下作業，因而圖6及7中所示電路之此種切換 作業能夠》施，以便使輸出變動最小，而能降低漣波成 分。當根據本發明換流器裝置使用在，例如，放電燈起 動裝置時，因此，能夠限制放電燈做為負載La發生之諸 如閃爍之問題。當然，可能如習用技術具有其可應用電 路之相同方式，保持输入功因之改善。 如果當上述換流器電路11在不同振盪頻率f=f〇下作 業時，本發明採用一種布置用來降低漣波成分，其如圖 2 (b)或（d)因此沒有任何措施變得較大。參照圖10,根 據本發明之控制裝置，包含供應電壓檢波器12用來檢測 電源電壓％η、頻率控制器13用來根據檢波器12之檢波 輸出控制換流器電路11之振盪頻率f 、驅動裝置14用來 接收頻率控制器13之輸出並可控制地驅動交換元件Q1及 Q2對。根據圖1Q之布置，因此，換流器電路11之振盪電 路頻率f ，能根據深受有關漣波成分發生影響之電源電 壓vin之變動而變動，而能有效地降低漣波成分。 本實施例中，負載La經變壓器T連接到諧振電容器C2 ，且自電源側絶緣，但電路作業沒有不同於負載直接成 -1 0 - --------------I!--------裝------.玎-----^ (請先閲讀背面之注意事項再填寫本頁) 本紙張尺度適用中國國家標準（CNS) f !規格（210 X 297公發） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 B6五、發明説明（9 ) 並聯於電容器C2之觀點。如此亦適用於電容器C2及負載 La連接到變壓器T之非電源侧，邸，在二次側上之倩形 〇 更明確地，對頻率f不同於漣波成分能夠降低之頻率 fo ,電源電®Vin及換流器電路11输出間之開係己經獲 得，其所得曲線如圖11中所示。如自圖示顯然可見，有 表示此種待性為，其當換流器電路11之振盪頻率f成為 f < f 0時，輸出亦因電源轚壓V in增加而成為更大 ，且输出v^t之增加因振盪頻率f自f0分離（即fu< in < f 13 < f 14 < f o )而形成更大。在此假設，例如，電源 電壓Vin在頻率fu時為0而輸出Lut為V i，則輸出 V〇ut能以變動換流器電路11之振盪頻率f饗應電源電壓 Vin而成為Vi，如自圖11將清楚可見。進一步假設電源 電壓是Vinl ,而換流器軍路11之振盪頻率f是fu，則 输出VC5Ut是^^1，或，當電源電壓是Vin2而換流器電路 1 1之振盪頻率f是f is，則輸出V 亦成為V丄。 本情形中，圖1 0實施例之換流器電路1 1之振盪頻率f ，根據電源電壓Vin之變動，以頻率控制器13而平流地 變動β即，如將立即理解，換流器電路11之振盪頻率f ，當電源電壓vin升高時，在周期中保持較低，但，相 反地，當電源電壓vin下降時，換流器電路11之振盪頻 率f提高。 雖然上述中，在振盪頻率f低於使漣波最小之頻率 -1 1 - (請先閱讀背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲·!規格（210 X 297公釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 __B6_ 五、發明説明（10) f 0時，h經提到輸出V^ut之控制為常數，但以相同布 置，可能在頻率f高於使漣波成分最小之頻率fo時， 控制輸出VQut為常數，如圖12所示（f21_f24 :在此fo <f21 <f22 <f23 <f24 )β 雖然較佳地，根據電源電M vin所選之換流器電路11 之振盪頻率f是得自圖11及12持性之一，但亦可能甚至 以變動大致成比例於電源電壓vin之頻率方式，如比較 於頻率没有控制之情形時，顯箸地降低漣波成分《進一 步，其中振盪頻率f成為fo情形之輸出，如圖8 中清楚所示，和其中頻率f成為可變之情形者有差異， 但如己參照圖11及12所說明，換流器電路11之輪出 保持為Vi及¥2之常數。因而，可能得到換流器電路11 之輸出，同時使用控制裝置充分降低漣波成分，其 中前述圖8之布置、及參照圖11及12所説明之進一步布 置组合如圖13所示。 圖14所示進一步實施例中，該電路布置不同於前述實 施例在於，包括換流器電路11之負載La之振盪条統方面 ，其連接到第1交換元件Q1之側，電容器C4之連接點及 二極體D3以及二極體D3之方向，根據振盪条統上述’接線 修正，且在橋式二極體DB輸出端檢測電源電壓Vin，但 是換流器電路11及降低漣波成分之功能大致和前述實施 例相同。 圖15所示另一實施例中，有不同於前述實施例方面， -1 2- (請先閲讀背面之注意事項再填寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4规格（2]0 X 297公釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 _B6_ 五 '發明説明（11) 在於DC成分削除電容器C3及，如情況需要，串聯阻抗用 途電容器C4之電感器L2額外接線之插入位置（電感器如 圖示中括號所示）；同時換流器電路11作業以及降低漣 波成分之功能，大致和前述實施例相同。在本實施例裝 置中，換流器電路11之振盪糸統中，額外提供電感器或 電容器亦很有用。 S —方面，如果負載La是放電燈，則需考慮其起動用 來減光。在放電燈中，換流器型之起動裝置，不具有輸 入功因改善電路包含電容器C4及二極體D3，減光起動能 以自包含電感器L1及電容器C2之第1振盪条統諧振頻率 之頻率偏離，使供應到放電燈之功率變得較小來執行。 在此，圖1之前述換流器裝置中，換流器電路之只有振 盪頻率變動造成漣波成分增加很多，如已提及以致如果 放電燈使用做為負載La情形時造成閃爍發生，在其上之 振鹽条統阻抗及換流器電路兩者變動，以致使輸出供應 到放電燈做為負載La、及漣波成分較小、且在新電路咀 抗中得到f = f〇之狀況，因而甚至在減光狀況能供應穩 定電流到放電燈，而能消除閃爍及類似問題。本情形中 ，列舉有二種方式，其中之一之振盪条統阻抗，根據換 流器電路11振盪頻率變動而變動，而其另一値之換流器 電路11頻率，根據振盪条統阻抗變動而變動。 圖16所示另一實施例中，對照圖1中前述電路布置， 有使用可飽合電抗器Lc替代電感器LU可飽合電抗器Lc -1 3- --------------II --------裝------，玎-----^ (請先閱讀背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4规格（210 X 297公釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 B6五、發明説明（12) 包含輸出繞組及控制繞組He ,通過控制繞組Ne之 電流受電抗器控制電路15所變動，而因而輸出繞組γ 之感抗成為可變動β電抗器控制電路15為控制電路13所 控制，提供用於交換元件£11及£12之作業，而驅動電路 14是根據控制電路13之輸出而可控制驅動交換元件Qt 及Q 2。 如果當圖16之換流器裝置用做為放電燈起動裝置，來 完全起動放電燈做為負載La,則換流器電路11之振盪頻 率成為f〇 ,而該布置形成，使得可飽和電抗器Lc之輪 出嬈組和兩個電容器C2及C4所形成兩痼振盪条統，將提 供大致如振盪在頻率fo之相同輸出。實施減光起動中 ,所造成流經由抗器控制電路15到可飽合電抗器控制繞 組1^之電流，為控制電路13所變動，而使輸出繞組Nl 之電烕值變動，且同時換流器電路11之振盪頻率以控制 電路13造成可變動，使兩値振盪条統之輸出為常數，因 而實現較小漣波成分之電源，且放電燈做為負載La能在 穩態中受到減光起動β本情形中，以輸出功因改善電路 亦能保持在輸入功因之改善效果而没有惡化。 實施減光起動中，進一步，該布置亦可使得換流器電 路11之振盪頻率成為控制電路13所控制而可變動，電流 以控制電路13經電抗器控制電路15供應到可飽合電抗器 Lc之控制繞組，以便在可變頻率下大致均等兩値振 盪条統之輸出，且使輸出繞組卩!^之電感值變動，而放 -1 4 - -------------r I --------裝------，玎-----^ (請先閲讀背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4规格（210 X 297公釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印焚 A6 __B6_ 五、發明説明（13) 電燈做為負載La,能以漣波成分降低及在穩態中經過減 光起動。在此，因為換流器電路11之輸出，隨電源電壓 Vin變動而變動，如圖8所見，亦可布置裝置使得，如 圖17所示，裝置提供用來檢測電源電壓Vin，而造成控 制電路13致動，使輸出繞組％之電感值，經電抗器控 制電路15根據電源電鼷Vin之變動而變動。 圖18所示再S —實施例中，提議更實際布置之可飽合 電抗器Lc及電抗器控制電路15，其中可飽和電抗器Lc以 兩値電抗器Lei及Le2來形成，這些電抗器之控制繞組 及極性相反，且連接到電抗器控制電路1 5，以電 阻器Rc、及可自由變動施加電壓之控制電源Vc成串聯接 線之等效方式來表示。根據該布置，輸出繞組 之飽合狀況成為較緩和，且控制變得更容易。 如圖19所示本發明S —實施例中，可飽合電抗器Lc以 串聯接線之電liLl及變壓器T1之一次嬈組Ml來替代，同 時變壓器之二次繞組N2並聯連接到可變阻抗Z及開關元 件SU在此，隨變壓器T1之二次嬈組為二次繞組N2所跨 接開關元件S1之開啓而短路，沒有出現一次徺組N1之電 感成分，但當二次繞組N2開路時出現有電威成分L2,且 電感值以控制可變阻抗元件Z之阻抗值，形成可變動在 0到L2之範圍内。即，.當振盪条統及電感器L1之電烕值 分別為L及L1時，其能適當地變動在L1<L<L1 + L2之範圍 内。 - 1 5 - --------------II --------裝------1T-----^ (請先閲讀背面之注意事項再塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297公釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 B6 五、發明説明U4) 如圖20所示本發明另一實施例中，電威器L2能經並聯 開關元件S2連接到電感器L1。在此，開朗元件S2可經開 啓/關閉控制，例如，如圖16所使用此種控制電路13之 控制。因而，開關元件S2之關閉狀況中，振盪条統之電 感將只是電感器L1之電感而己，然而振盪糸統之電威在 一經開啓開關元件S2,即為電烕器L1及L2之電感合成β 雖然，在上述中已參照振潘条統之電感變動使振盪糸 統阻抗可變之情形說明，但變動電容器C4或C2之電容亦 有用。 圖2 1所示本發明另一實施例，電容器C5及開關元件S3 並聯連接電容器C4，用做為阻抗元件，以便在較佳地此 種控制電路13之控制下成為開啓及關閉，如圖16中所使 用，且阻抗能以開關元件S3之開啓及關閉來切換。 圖22所示本發明進一步實施例中，電容器C6及開關元 件S4之串聯電路並聯連接到電容器C2,且開關元件S4較 佳地在圖13所使用之控制電路13之控制下，形成開啓及 關閉以便阻抗能切換。 通常，情形不是電容器C4之充電時間和如前所述之交 換元件Q1及Q2之開啓及關閉同時發生，而是，時間決定 於跨接電容器C4之電壓Ve4、電源電壓Vin、跨接電感器 L1之電壓及跨接電容器C3之電壓Ve3所成關係，及兩 個振盪条統間切換加諸於漣波成分發生之影輾。似是而 非地說，輸出待性能以控制電容器C4之充及放電時間來 -1 6 - (請先閲讀背面之注意事項再塡寫本頁) -丨裝- '11. 線_ 本紙張又度適用中國國家標準（CNS)甲4規格（210 X 297公釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 B6_ 五、發明説明（15 ) 變動，但似乎，變動電容器C4之咀抗將更簡單》 圖2 3所示再另一實施例中，採用以控制電容器C4之充 及放電時間之方式，來大致均等兩镅振盪条統输出。本 情形中，開關元件S5串聯連接到二極體D3,同時該二極 體D3及開瞒元件S5能以單向開關元件來替代。圖23實施 例中，當交換元件Q1開啓、且控制開關元件S 5時，電容 器C4成為可經交換元件Q1放電，因而電容器C4内累積能 量之放電比降低，次一可充電量變小，而充及放電兩者 之期間能縮短。如此，電容器C4之表面容童可以變動， 且以實施控制成為能獲得包含較少漣波成分之輸出，以 便大致均等兩値振盪糸統之輸出，如圖21實施例中相同 方式》 圖2 4所示本發明另一實施例中，分別有兩値開關元件 S〇l及S 02，'連接到_成橋式1:1極8^ D B之各=極88 D03及 DQ4，使得當交換元件Q2開啓時，根據電壓之前逑關傜 ，以開關元件Sm及S%控制電容器C4之充電及放電。在 此，流到該開關元件及S%之電流切換視電源電壓之 極性而定，但橋式二極體作業是決定電流將流到那一傾 開關元件及,所以甚至當開關元件sQ1及台的同時 開啓及關閉時，亦沒有問題發生在此時，以降低電容 器C4之充電量，能造成電容器C4之次一放電時間延遲， 以便使充電及放電之兩者期間縮短，且最後電容器C4之 表面容量變動，以便能得到較少漣波成分之输出，如前 -1 7 - -----------------------裝------、玎-----h Ή (請先閲讀背面之注意事項再填寫本頁) 本紙張夂度適用中國國家標準（CNS)甲4规格（210 X 297公诠） 82. 5. 20,000 A6 B6 經濟部中央標準局員工消費合作社印製 五、發明説明（16) 述實施例之相同方式。 圖25所示本發明進一步實施例，對照圖24之實施例， 開關元件S μ串聯連接橋式二極體DB内之另一二極體 ，而本布置能如圖24相同方式作業。如此，圖23至25實 施例中値別開關元件S 5、及S%，能防止一連接到電 源時之任何衝流，因為其成為同步於AC電源Vs之零交點 而開啓。 圖26中，所示為本發明另一實施例，其中開關元件S6 插入和電容器C4成串聯，能使電容器C4之充電及放電可 共同控制。進一步在画27中所示，甚至當開關元件S7插 入電路中之AC電源Vs及橋式二極體DB之間，能得到相同 控制。 本發明特擞電路布置，亦可使用在不同於前述實施例 之電路中。圖28所示進一步實施例中，布置使得電容器 C3和電容器C2及C4串聯連接橋式二極體DB之輸出端。如 圖29另一實施例所示，進一步，布置中提供電感器L3在 電容器C4及C2之間。雖然画28及29實施例中，用於漣波 成分降低之布置，能夠使如圖16實施例所使用者，但亦 可使用參照圖18至26所提及用於漣波成分降低之此種布 置。亦可能進一步包括電感器或電容器在換流器電路11 之振盪条統内。 圖30中，所示為本發明再另一實施例，其中提供額外 方式來防止一連接到電源時之衝流，同時如圖1之大致 -1 8 - -------------,——一---------裝------'叮----- (請先閲讀背面之注意事項冉塡寫本頁) 本紙張尺度適用中國國家標準（CNS)甲4规格（210 X 297公釐） 82. 5. 20,000 經濟部中央標準局員工消費合作社印製 A6 _B6_ 五、發明説明（17 ) 相同布置使用於所有其他部份。本實施例特戡在添加衝 流防止方式。在一接線到電源時，卽造成衝流流動，當 大容量之電容器（較佳地，電解電容器）瞬間充電，其 電流值為靜態輸入電流之數十倍到百數十倍之大小，而 容易發生問題諸如電路斷路器斷路、電源開關接點熔接 及類似情形。本發明中，因此，二極體D 5在一經接線到 電源時，不造成電容器充電之方向，串聯連接大容量電 容器C1,而以二極體D 5能防止在一經接線到電源時流進 電容器C1之衝流。進一步，' 為了電容器C1在交換元件Q1 及Q2之開啓時間期間能充電，二極體D4連接在電容器C1 之接線點到二極體D5及負載La之接線點到電慼器L1間之 陰極側上。 在此，當交換元件Q2開啓時，電容器C1之能量即流經 橋式二極體DB、二極體D3、電容器C1、二棰體D4、電威 器L1及交換元件Q2之路線β在一關閉交換元件Q2時，電 感器L1中所累積能量即造成電流流經電感器L1、二極體 D1、電容器C1及二極體D4之路線，而實施電容器C1之充 電。即，電壓降抗流器電路以電容器CU二極體D4、電 感器L1、交換元件Q2及二極體D1來構成，而能夠有效地 以實施控制在一經電源接線時，即逐漸放大交換元件Q2 之開啓任務來消除衝流問題。 圖31所示本發明再另一實施例，不同於圖30實施例， 同樣在電容器C5連接在二極體D3之連接點到電容器C1、 -1 9- 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297公釐） 82. 5. 20,000 -------------II .--------裝------.玎-----^ {請先閲讀背面之注意事項再塡寫本頁) A6 B6 經濟部中央標準局員工消費合作杜印製 五、發明説明（18) 及放電燈做為負載La之連接點到電容器C3之間，雖然其 他布置如圖30—樣。電容器C5功能類似電容器C3用於削 除DC成分β在此，在前述半橋式換流器電路情形中，甚 至沒有諸如圖31所示電容器C3及C5情形時，作業亦大致 不變。另一方面，當採取以插入二極鱷D3及D5之方式防 止衝流時，失去根據本發明之放電燈起動裝置内所要包 括換流器電路之一再生電流回路。即，圖30實施例情形 中，一經關閉交換元件Q2時，即必需有經二極體D1反餓 到電威器L1及電容器C2所構成之振盪条統中振盪電流電 容器C1,但是因為二極體D5存在，没有再生電流流動。 因而，經電感器L1累積能量造成電流流經電感器L1、二 極體D1、電容器C1及二極體D4之路線，而電感器L1及電 容器C2沒有振盪作用發生，因而整個換流器電路之振盪 作用減弱，而降低跨接在放電燈La所産生之電壓，以致 尤其一在起動燈時，即不能施加任何充分大起動電壓到 放電燈La，而造成放電燈La不能以平流方式實施之問題 發生〇 本實施例中，在交換元件Q2關閉時，電容器C5提供有 效地形成流經電感器L1、二極體D1、電容器C5、放電燈 La及電容器C2之再生電流路線，使得換流器電路振盪減 弱能夠避免。以該布置，形成可能施加充分起動電壓到 放電燈La。 圖32所示另一實施例中，電容器C6連接到電容器Cl及 -2 0 - (請先閲讀背面之注意事項再塡寫本頁) -裝. 'ΤΓ 碌. 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297公發） 82. 5. 20,000 A6 B6 五、發明説明（19) 二極體D1之串接電路兩端， ，即造成再生電流流經電慼 、電容器C3、放電燈La及電 進一步實施例中，所採防止 實施例相同。雖然在圖30至 電路，但必需理解，用於漣 ，如參照圖10及類似圖示所 其中在交換元件Q2—關閉時 器L1、二極體D1、電容器C6 容器C2之路線。圖33至36之 衝流之方式因而大致和前述 36實施例中，没有表示控制 波成分降低之此種控制電路 提及，能適當地提供。 (請先閲讀背面之注意事項再塡寫本頁) 經濟部中央標準局員工消費合作社印製 本紙張尺度適用中國國家標準（CNS)甲4規格（210 X 297公釐） 82. 5. 20,000I Printed by A6 __B6_ of the Consumer Cooperatives of the Central Standards Bureau of the Ministry of Economic Affairs. 5. Description of the Invention (7) The impact of the system is large, and when the current voltage V. is large, the load current i1a becomes m la smaller, as shown in Figure 2 (d ) Shown in β when f = f1, where ila of the first oscillating system is smaller than ila of the second oscillating system, on the contrary, when the power supply voltage Vin increases, the load current ila will increase as shown in the waveform of Fig. 2 (b). Show. Therefore, the condition where the ripple component of the load current ila becomes the smallest can be regarded as f = f0, where ila of the first oscillation system is approximately equal to ila of the second oscillation system. Because in this case, a ripple directly contributes to the occurrence of ripples. It is the supply voltage vin of the power supply voltage vin, and the output characteristics (actually, the absolute value of the power supply voltage Vin2 丨 Vin I, because the channel source voltage is passed through the bridge diode Supplied to its next level circuit, and has obtained a converter device, as shown in Figure 8, where the output (for example, the voltage across the load) is placed on the vertical coordinate, and the absolute value of the power supply voltage is placed on the horizontal coordinate In the figure, the absolute value of the difference is an instantaneous value, and it also indicates the maximum value VP of the power supply voltage. When the converter device in FIG. 1 is used, the absolute value of the power supply voltage IV in I and the output voltage are shown in FIG. In this situation shown in 9, the output V at IV in I = 0 can be obtained from the value of the short period At at before and after t = ', and the output V at 丨 | = VP can also be in out is obtained during a short time period At before and after t = t3 ', and likewise, the output at any I vin I can be obtained before and after the time I vin | arrives (eg, t = t 2) The value of the short time △ t. Here, the short time At must be optimally set several times as large as The frequency of the switching element used in the current transformer circuit makes any 丨 vini changeable -9- (Please read the precautions on the back before writing this page) This paper size applies to China National Standard (CNS) A4 specification (210 X 297) 82. 5. 20,000 A6 _B6_ printed by the Consumer Cooperatives of the Central Bureau of Standards of the Ministry of Economic Affairs 5. Explanation of the invention (8) The level of neglect. As apparent from Figure 8, when the oscillation frequency of the inverter circuit 11 When f = f0 ′, the output becomes substantially constant and the ripple component can be reduced. According to the embodiment of FIG. 1 of the present invention, a control device 11a is provided, so that the output of the inverter circuit 11 in the two-wave oscillation system will be Operation at approximately equal frequencies f0, so this switching operation of the circuits shown in Figs. 6 and 7 can be implemented in order to minimize output fluctuations and reduce ripple components. When the inverter device according to the present invention is used In, for example, a discharge lamp start-up device, it is therefore possible to limit problems such as flicker occurring in the discharge lamp as a load La. Of course, it may be possible to keep the same way as conventional technology has its applicable circuits, keeping The power factor is improved. If the inverter circuit 11 operates at different oscillation frequencies f = f0, the present invention adopts an arrangement to reduce the ripple component, which is shown in Figure 2 (b) or (d). It becomes larger without any measures. Referring to FIG. 10, the control device according to the present invention includes a supply voltage detector 12 for detecting the power supply voltage% η, and a frequency controller 13 for controlling the inverter based on the detection output of the detector 12. The oscillating frequency f of the circuit 11 and the driving device 14 are used to receive the output of the frequency controller 13 and controllably drive the pair of switching elements Q1 and Q2. According to the arrangement of Fig. 1Q, therefore, the frequency f of the oscillating circuit of the inverter circuit 11 can be changed according to the variation of the power supply voltage vin which is deeply affected by the relevant ripple components, and the ripple components can be effectively reduced. In this embodiment, the load La is connected to the resonance capacitor C2 via the transformer T and is insulated from the power source side, but the circuit operation is not different from the load directly becoming -1 0--------------- I ! -------- Installation ------. 玎 ----- ^ (Please read the precautions on the back before filling in this page) This paper size applies to China National Standard (CNS) f! Specifications (Issued by 210 X 297) 82. 5. 20,000 A6 B6 printed by the Consumer Cooperatives of the Central Standards Bureau of the Ministry of Economic Affairs 5. Description of the invention (9) View of parallel connection to capacitor C2. This also applies to the capacitor C2 and the load La connected to the non-power supply side of the transformer T, and the shape on the secondary side. More specifically, the frequency fo, which is different from the ripple component frequency, can be reduced. The opening between Vin and the output of the inverter circuit 11 has been obtained, and the resulting curve is shown in FIG. 11. As can be clearly seen from the figure, it is indicated that this kind of standby is that when the oscillation frequency f of the inverter circuit 11 becomes f < f 0, the output also becomes larger due to the increase of the power supply voltage V in, and the output The increase in v ^ t is greater because the oscillation frequency f is separated from f0 (that is, fu < in < f 13 < f 14 < fo). It is assumed here that, for example, when the power supply voltage Vin is 0 at the frequency fu and the output Lut is Vi, the output Vout can change the oscillation frequency f of the inverter circuit 11 to become Vi in response to the power supply voltage Vin. Figure 11 will be clearly visible. It is further assumed that the power supply voltage is Vinl and the oscillation frequency f of the converter circuit 11 is fu, then the output VC5Ut is ^^ 1, or when the power supply voltage is Vin2 and the oscillation frequency f of the inverter circuit 11 is f is , The output V also becomes V 丄. In this case, the oscillation frequency f of the inverter circuit 11 of the embodiment of FIG. 10 is fluctuated by the frequency controller 13 in a smooth manner according to the change of the power supply voltage Vin, ie, as will be understood immediately, the inverter circuit 11 The oscillation frequency f of the inverter circuit 11 increases when the power supply voltage vin increases, but conversely, when the power supply voltage vin decreases. Although in the above, the oscillation frequency f is lower than the frequency that minimizes the ripple -1 1-(Please read the precautions on the back before writing this page) This paper size applies the Chinese National Standard (CNS) A ·! Specifications (210 X 297 mm) 82. 5. 20,000 A6 printed by the Consumer Cooperatives of the Central Standards Bureau of the Ministry of Economic Affairs __B6_ V. Description of the invention (10) When f 0, h is referred to as a constant output V ^ ut control, but with the same arrangement It is possible that when the frequency f is higher than the frequency fo which minimizes the ripple component, the control output VQut is constant, as shown in FIG. 12 (f21_f24: where fo < f21 < f22 < f23 < f24) β although Preferably, the oscillation frequency f of the inverter circuit 11 selected according to the power source M vin is obtained from one of the persistences of FIGS. 11 and 12, but it may even be a frequency manner that is approximately proportional to the power supply voltage vin, such as Compared with the case where the frequency is not controlled, the ripple component is significantly reduced. "Further, the oscillation frequency f becomes the output of the fo case, as clearly shown in Fig. 8, which is different from the case where the frequency f becomes variable. However, as explained with reference to Figs. Vi and the holding of ¥ 2 constant. Therefore, it is possible to obtain the output of the inverter circuit 11 while using the control device to sufficiently reduce the ripple component. The arrangement of FIG. 8 described above and the further arrangement combination described with reference to FIGS. 11 and 12 are shown in FIG. 13. In the further embodiment shown in FIG. 14, the circuit arrangement is different from the previous embodiment in that the oscillation system including the load La of the inverter circuit 11 is connected to the side of the first switching element Q1 and the connection point of the capacitor C4 And the direction of diode D3 and diode D3, according to the above-mentioned 'wiring correction of the oscillation system, and the power supply voltage Vin is detected at the output of the bridge diode DB, but the inverter circuit 11 and the function of reducing the ripple component It is substantially the same as the foregoing embodiment. In another embodiment shown in FIG. 15, there are aspects different from the previous embodiment, -1 2- (Please read the precautions on the back before filling this page) This paper size is applicable to China National Standard (CNS) A4 specification (2 ] 0 X 297 mm) 82. 5. 20,000 Printed by A6 _B6_ of the Consumer Cooperatives of the Central Bureau of Standards of the Ministry of Economic Affairs of the People's Republic of China (5) Invention Description (11) The DC component is used to remove capacitor C3 and, if necessary, the impedance of series capacitor C4 The insertion position of the additional wiring of the converter L2 (the inductor is shown in the brackets in the figure); at the same time, the inverter circuit 11 operates and the function of reducing the ripple component is substantially the same as the previous embodiment. In the apparatus of the present embodiment, it is also useful to additionally provide an inductor or a capacitor in the oscillation system of the inverter circuit 11. S — On the other hand, if the load La is a discharge lamp, its start-up needs to be considered for dimming. In a discharge lamp, a converter-type starting device does not have an input power factor improving circuit including a capacitor C4 and a diode D3, and the dimming start can be achieved by the resonance frequency of the first oscillation strip including the inductor L1 and the capacitor C2. The frequency deviation is performed so that the power supplied to the discharge lamp becomes smaller to perform. Here, in the aforementioned inverter device of FIG. 1, only the fluctuation of the oscillation frequency of the inverter circuit causes the ripple component to increase a lot. As already mentioned, if the discharge lamp is used as the load La, the flicker occurs. Both the impedance and the inverter circuit of the upper oscillator are changed, so that the output is supplied to the discharge lamp as a load La, and the ripple component is small, and f = f0 is obtained in the new circuit impedance. Therefore, even in a dimmed condition, a stable current can be supplied to the discharge lamp, and flicker and the like can be eliminated. In this case, there are two ways listed, one of which oscillates the impedance according to the oscillation frequency of the inverter circuit 11 changes, and the other one of the inverter circuit 11 changes the frequency according to the oscillating system impedance And change. In another embodiment shown in FIG. 16, compared to the circuit arrangement in FIG. 1, there is a use of a saturable reactor Lc instead of the inductor LU saturable reactor Lc -1 3- ---------- ---- II -------- Installation ------, 玎 ----- ^ (Please read the precautions on the back before writing this page) This paper size applies Chinese national standards ( CNS) A4 specification (210 X 297 mm) 82. 5. 20,000 A6 B6 printed by the Consumer Cooperatives of the Central Standards Bureau of the Ministry of Economic Affairs 5. Description of the invention (12) Including the output winding and control winding He, the current through the control winding Ne The reactor control circuit 15 is changed, and thus the inductive reactance of the output winding γ becomes variable. The β reactor control circuit 15 is controlled by the control circuit 13 and provides operations for exchange components of £ 11 and £ 12, and the drive circuit 14 The drive switching elements Qt and Q 2 can be controlled based on the output of the control circuit 13. If the inverter device of FIG. 16 is used as a discharge lamp starting device to fully start the discharge lamp as a load La, the oscillation frequency of the inverter circuit 11 becomes f0, and this arrangement is formed so that the saturable reactor The L2 wheel-out group and the two capacitors C2 and C4 form a two-line oscillation system that will provide approximately the same output as the frequency at the frequency fo. In the implementation of the dimming start, the current flowing through the reactor control circuit 15 to the saturable reactor control winding 1 ^ is changed by the control circuit 13 to change the electrical threshold value of the output winding N1 and commutate at the same time. The oscillating frequency of the generator circuit 11 can be changed by the control circuit 13 so that the output of the two oscillating systems is constant, so that a power source with a small ripple component is realized, and the discharge lamp as a load La can be dimmed in a steady state. Starting β In this case, the output power factor improvement circuit can also maintain the improvement effect of the input power factor without deterioration. In the implementation of the dimming start, further, this arrangement can also make the oscillation frequency of the inverter circuit 11 controlled by the control circuit 13 and can be changed. The current is supplied to the saturable reactor Lc by the control circuit 13 through the reactor control circuit 15 Control the winding so that the output of the two oscillating strips is approximately equalized at a variable frequency, and the inductance of the output winding 卩! ^ Is changed, and -1 4------------- -r I -------- install ------, 玎 ----- ^ (Please read the precautions on the back before writing this page) This paper size applies to Chinese National Standards (CNS) A4 specifications (210 X 297 mm) 82. 5. 20,000 Printed by the Consumers' Cooperative of the Central Standards Bureau of the Ministry of Economic Affairs A6 __B6_ V. Description of the invention (13) The electric lamp as the load La can be reduced by the ripple component and in a steady state Start after dimming. Here, because the output of the inverter circuit 11 changes with the change of the power supply voltage Vin, as shown in FIG. 8, a device can also be arranged so that, as shown in FIG. 17, the device provides a control circuit for detecting the power supply voltage Vin, resulting in a control circuit. 13 is actuated, so that the inductance value of the output winding% changes through the reactor control circuit 15 according to the change of the power supply voltage Vin. As shown in FIG. 18, in the embodiment, a more practical arrangement of a saturable reactor Lc and a reactor control circuit 15 is proposed. The saturable reactor Lc is formed by two reactors Lei and Le2. The control winding and the polarity are opposite, and are connected to the reactor control circuit 15, which is represented by the equivalent way that the resistor Rc and the control power source Vc of the freely variable applied voltage are connected in series. According to this arrangement, the saturation condition of the output winding becomes milder, and control becomes easier. As shown in FIG. 19 of the present invention S—In the embodiment, the saturable reactor Lc is replaced by a series-connected electric power liLl and a primary unit M1 of the transformer T1, and the secondary winding N2 of the transformer is connected in parallel to the variable impedance Z. And the switching element SU is here. As the secondary element of the transformer T1 is turned on and shorted by the switching element S1 bridged by the secondary winding N2, the inductance component of the primary element N1 does not appear, but it appears when the secondary winding N2 is open. There is electrical power component L2, and the inductance value is used to control the impedance value of the variable impedance element Z, which can be changed within the range of 0 to L2. That is, when the electrical values of the oscillating system and the inductor L1 are L and L1, respectively, they can be appropriately changed within the range of L1 < L < L1 + L2. -1 5--------------- II -------- install --------- 1T ----- ^ (Please read the precautions on the back first (Written on this page) This paper size applies to China National Standard (CNS) A4 specification (210 X 297 mm) 82. 5. 20,000 A6 B6 printed by the Consumer Cooperatives of the Central Standards Bureau of the Ministry of Economic Affairs 5. Description of the invention U4) In another embodiment of the present invention shown in FIG. 20, the electric conductor L2 can be connected to the inductor L1 via the parallel switching element S2. Here, the cheerful element S2 can be controlled by on / off, for example, control using such a control circuit 13 as shown in FIG. Therefore, in the closed state of the switching element S2, the inductance of the oscillation system will be only the inductance of the inductor L1. However, once the switching system S2 is turned on, the inductance of the oscillation system L1 and L2 is combined. β Although the above description has been made with reference to the case where the inductance of the oscillating system changes the impedance of the oscillation system, it is also useful to change the capacitance of the capacitor C4 or C2. FIG. 21 shows another embodiment of the present invention. The capacitor C5 and the switching element S3 are connected in parallel with the capacitor C4 as an impedance element so as to be turned on and off under the control of such a control circuit 13 as shown in FIG. 16. The impedance can be switched by turning on and off the switching element S3. In a further embodiment of the present invention shown in FIG. 22, the series circuit of the capacitor C6 and the switching element S4 is connected in parallel to the capacitor C2, and the switching element S4 is preferably turned on and off under the control of the control circuit 13 used in FIG. So that the impedance can be switched. In general, the situation is not that the charging time of capacitor C4 and the opening and closing of switching elements Q1 and Q2 as described above occur at the same time, but that the time is determined by the voltage Ve4, the power supply voltage Vin, and the jumper inductor L1 of the jumper capacitor C4. The relationship between the voltage of the capacitor and the voltage Ve3 across the capacitor C3, and the switching between the two oscillation bars is added to the shadow component. Paradoxically, the output standby performance is to control the charge and discharge time of capacitor C4 to -1 6-(Please read the precautions on the back before writing this page)-丨 Installation-'11. 线 _ This paper is again suitable for China National Standard (CNS) A4 Specification (210 X 297 mm) 82. 5. 20,000 Printed by the Consumers' Cooperative of the Central Standards Bureau of the Ministry of Economic Affairs A6 B6_ V. Description of Invention (15) Changes, but it seems that the capacitor C4 nozzle resistance It will be simpler "As shown in Fig. 23, in another embodiment, the charging and discharging time of the capacitor C4 is controlled to substantially equalize the output of the two oscillating bars. In this case, the switching element S5 is connected in series to the diode D3, and the diode D3 and the opening element S5 can be replaced by unidirectional switching elements. In the embodiment of FIG. 23, when the switching element Q1 is turned on and the switching element S5 is controlled, the capacitor C4 can be discharged through the switching element Q1. Therefore, the discharge ratio of the accumulated energy in the capacitor C4 is reduced, and the next rechargeable capacity is reduced, and the And the period of both discharge can be shortened. In this way, the surface capacity of the capacitor C4 can be changed, and the control can be implemented to obtain an output that contains fewer ripple components, so that the output of the two oscillation systems is approximately equal, as shown in the same manner in the embodiment of Fig. 21 "Fig. 2 4 In another embodiment of the present invention as shown, there are two switching elements S01 and S02, respectively, which are connected to a bridged 1: 1 pole 8 ^ DB each = pole 88 D03 and DQ4, so that when the switching element When Q2 is turned on, the capacitor C4 is controlled to charge and discharge with the switching elements Sm and S% based on the voltage before the voltage is turned off. Here, the switching of the current flowing to the switching element and S% depends on the polarity of the power supply voltage, but the bridge diode operation determines the current that will flow to the tilting switching element, so even when the switching element sQ1 and the stage When it is turned on and off at the same time, no problem occurs at this time. In order to reduce the charge amount of capacitor C4, it can cause the next discharge time of capacitor C4 to delay, so as to shorten the period between charging and discharging. The surface capacity is changed so as to get the output of less ripple components, such as the previous -1 7------------------------ installation ----- -, 玎 ----- h Ή (Please read the notes on the back before filling this page) This paper is suitable for China National Standard (CNS) A4 specifications (210 X 297 public interpretation) 82. 5. 20,000 A6 B6 Printed by the Consumers' Cooperative of the Central Standards Bureau of the Ministry of Economic Affairs 5. Description of Invention (16) The same way as in the embodiment described above. FIG. 25 shows a further embodiment of the present invention. In contrast to the embodiment of FIG. 24, the switching element S μ is connected in series to another diode in the bridge diode DB, and the arrangement can be operated in the same manner as in FIG. 24. In this way, the separate switching elements S5 and S% in the embodiments of Figs. 23 to 25 can prevent any inrush current when connected to the power source because it is turned on synchronously with the zero crossing point of the AC power source Vs. In Fig. 26, another embodiment of the present invention is shown, in which the switching element S6 is inserted in series with the capacitor C4, so that the charging and discharging of the capacitor C4 can be controlled together. As further shown in Fig. 27, the same control can be obtained even when the switching element S7 is inserted between the AC power source Vs and the bridge diode DB in the circuit. The special circuit arrangement of the present invention can also be used in circuits different from the foregoing embodiments. In a further embodiment shown in Fig. 28, the arrangement is such that capacitor C3 and capacitors C2 and C4 are connected in series to the output terminal of the bridge diode DB. As shown in another embodiment of FIG. 29, further, an inductor L3 is provided in the arrangement between the capacitors C4 and C2. Although the arrangement for reducing the ripple component in the embodiments of 28 and 29 can be used by the user of the embodiment of FIG. 16, the method for reducing the ripple component mentioned in FIGS. 18 to 26 can also be used. Layout. It may further include an inductor or a capacitor in the oscillation system of the inverter circuit 11. In Fig. 30, there is shown another embodiment of the present invention, in which an additional method is provided to prevent an inrush current when connected to a power source, and at the same time, it is roughly -18---------- ---, —— 一 --------- install ------ 'ding ----- (Please read the notes on the back first and write this page) This paper size is applicable to China Standard (CNS) A4 specification (210 X 297 mm) 82. 5. 20,000 Printed by the Consumer Cooperatives of the Central Standards Bureau of the Ministry of Economic Affairs A6 _B6_ V. Description of the invention (17) The same arrangement is used in all other parts. This embodiment is specifically designed to add a surge prevention method. When a wire is connected to a power source, it causes a rush current. When a large-capacity capacitor (preferably, an electrolytic capacitor) is instantaneously charged, its current value is tens to hundreds of times the static input current, which is easy. Problems such as open circuit breakers, welding of power switch contacts, and the like occur. In the present invention, therefore, the diode D 5 does not cause the direction of capacitor charging when it is connected to the power source, and the large-capacity capacitor C1 is connected in series, and the diode D 5 can prevent the capacitor from flowing into the capacitor when it is connected to the power source. The rush of C1. Further, for the capacitor C1 to be charged during the on time of the switching elements Q1 and Q2, the diode D4 is connected between the connection point of the capacitor C1 to the connection point of the diode D5 and the load La to the cathode side of the capacitor L1. on. Here, when the switching element Q2 is turned on, the energy of the capacitor C1 flows through the bridge diode DB, the diode D3, the capacitor C1, the diode D4, the electric conductor L1, and the route β of the switching element Q2. When the switching element Q2 is turned off, the energy accumulated in the inductor L1 causes a current to flow through the route of the inductor L1, the diode D1, the capacitor C1, and the diode D4, and the capacitor C1 is charged. That is, the voltage drop reactor circuit is constituted by the capacitor CU diode D4, the inductor L1, the switching element Q2, and the diode D1, and can be effectively controlled once the power is connected, that is, the switching element Q2 is gradually enlarged. Open the mission to eliminate the flow problem. Another embodiment of the present invention shown in FIG. 31 is different from the embodiment of FIG. 30. Similarly, the capacitor C5 is connected to the connection point of the diode D3 to the capacitor C1, -1 9- This paper applies the Chinese National Standard (CNS) A4 specifications (210 X 297 mm) 82. 5. 20,000 ------------- II .-------- installation ------. 玎 --- -^ {Please read the notes on the back before copying this page) A6 B6 Printed by the Consumers' Cooperation Department of the Central Standards Bureau of the Ministry of Economic Affairs. 5. Description of the invention (18) and the discharge lamp as the connection point of the load La to the capacitor C3. Between, although other arrangements are like Figure 30. Capacitor C5 functions similarly to capacitor C3 to remove the DC component β. In the case of the aforementioned half-bridge inverter circuit, the operation is almost unchanged even when there are no capacitors C3 and C5 as shown in FIG. 31. On the other hand, when the inrush current is prevented by inserting the two-pole alligators D3 and D5, one of the regenerative current circuits to be included in the inverter circuit in the discharge lamp starting device according to the present invention is lost. That is, in the case of the embodiment of FIG. 30, once the switching element Q2 is turned off, the oscillation current capacitor C1 in the oscillation system composed of the electric power device L1 and the capacitor C2 must be anti-starved via the diode D1, but because the second electrode The body D5 exists and no regenerative current flows. Therefore, the accumulated energy through the inductor L1 causes a current to flow through the route of the inductor L1, the diode D1, the capacitor C1, and the diode D4, and no oscillation occurs in the inductor L1 and the capacitor C2. Therefore, the entire converter circuit The oscillation effect is weakened, and the voltage generated across the discharge lamp La is reduced, so that especially when starting the lamp, it is impossible to apply any sufficiently large starting voltage to the discharge lamp La, which causes the problem that the discharge lamp La cannot be implemented in a flat flow manner. Occurrence. In this embodiment, when the switching element Q2 is turned off, the capacitor C5 provides a regenerative current path that effectively flows through the inductor L1, the diode D1, the capacitor C5, the discharge lamp La, and the capacitor C2, so that the inverter circuit Reduced oscillations can be avoided. With this arrangement, it is possible to apply a sufficient starting voltage to the discharge lamp La. In another embodiment shown in FIG. 32, the capacitor C6 is connected to the capacitors Cl and -2 0-(Please read the precautions on the back before writing this page) -installation. 'ΤΓ .. This paper size applies Chinese national standards ( CNS) A4 specifications (210 X 297) 82. 5. 20,000 A6 B6 V. Description of the invention (19) The two ends of the series circuit of diode D1, which causes the regenerative current to flow through the capacitor, capacitor C3, In further embodiments of the discharge lamp La and electricity, the preventive embodiments adopted are the same. Although it is shown in Fig. 30 to the circuit, it must be understood that it is used for ripple, as shown in Fig. 10 and the like, in which the switching element Q2-the closing time of the timer L1, the diode D1, the capacitor C6, and the container C2 are used. The mode of the rush current in Figs. 33 to 36 is therefore roughly the same as in the aforementioned 36 embodiment, and such a control circuit that does not show a reduction in the control wave component can be provided appropriately. (Please read the precautions on the back before writing this page) Printed by the Consumer Cooperatives of the Central Bureau of Standards of the Ministry of Economic Affairs This paper is sized for China National Standard (CNS) A4 (210 X 297 mm) 82. 5. 20,000