TW201251269A - Charging system with adaptive power management - Google Patents

Abstract

An embodiment of a charger may include an input, at least one switch having a first node coupled to a reference voltage, a current sensor coupled between the input and a second node of the at least one switch, an output coupled to a third node of the at least one switch, and a charge controller coupled to the input to determine an input voltage, to the current sensor to determine an input current and to control inputs of the at least one switch. The at least one switch may be responsive to control signals supplied by the charge controller to the control inputs thereof to control voltage and current at the output of the charger. The charge controller may be responsive to the input voltage and the input current to produce the control signals in a manner that maximizes electrical power drawn at the input.

Description

201251269 VI. Description of the Invention: TECHNICAL FIELD OF THE INVENTION The present invention relates to a charging system, and more particularly to a charging system with adaptive power management. Priority Claims This is a partial continuation of US Non-Provisional Patent Application Serial No. 13/421,836, filed on March 15, 2002, and claims the rights and priority of the following patent applications: 2011 US Provisional Patent Application No. 61/478,575, dated April 25, 2015, US Provisional Patent Application No. 61/6〇4,226, 2〇12, 3 US Provisional Patent Application No. 61/617, 6〇9, which is filed on the 29th of the month. The disclosure of each of the aforementioned patent applications is hereby incorporated by reference in its entirety by reference in its entirety in the the the the the the the the the the the the the the the the the the the the the the The battery of the electronic circuit system inside the device. In addition, such devices can also be powered by a household AC (AC) power source by using a so-called AC adapter that plugs into the wall and converts the AC power signal into a direct current (DC) signal. Used to supply the required power to the device. The current supplied by the AC adapter is used to charge the battery of the electronic device and the electronic circuitry used to power the device. 'In general, every electronic device uses a dedicated AC adapter designed specifically for the device 4 201251269. For example, an electronic device may require 5 watts (W) of power '俾 such that a first AC adapter will provide 1 amp (A) of current at 5 volts (V) for a specified The amount of time is used to charge the battery of the electronic device. If the electronic device uses a second AC adapter with a rated power of only 2.5 watts and can only provide a maximum current of 〇5A at 5V, then this may result in an overload (〇verl〇ad) situation. And then caused the shutdown of the second AC adapter of s Xuan (shutd〇wn). Therefore, each electronic device requires its own dedicated AC adapter designed for the device. In operation, the majority of the current output by the AC adapter is provided while the battery in the electronic device is being charged. For example, if the current output by the AC adapter is 1A, then it may require 〇·〇5 to 0.1A to supply power to the electronic circuitry in the electronic device, while the remaining 0,9 to 〇.95Α will be used to charge the battery. This situation only exists when the battery is very low; when the battery is fully charged or nearly fully charged, the actual current drawn from the AC adapter will usually be the amount of electricity in the electron (4) The power required by the manager is, in other words, 〇.〇5 to 〇1A in this example. ▲ Ideally, the operation of an AC adapter or other input power source (eg, a solar panel array) would cause a load to change even if the electronic device is placed on the adapter. Get the maximum amount of energy at the device. By maximizing the amount of power provided by the AC adapter, the charging time of the battery in the electronic device is minimized. Since the operation of the 转接 Adapter to provide maximum power ensures that the maximum amount of current can be used to charge the battery in 201251269, the foregoing conditions will hold. SUMMARY OF THE INVENTION A feature of the present invention is: a bamboo & a charger comprising: an input; at least one switch having a first node broken into a reference voltage; a current a sensor that is coupled between the input and a second node of the at least one of the at least one of the at least one of the at least one of the at least one of the at least one of the third node; And a charge controller, which is coupled to the input and configured to be used to calculate an input voltage, coupled to the current sensor and configured to Using 1 for determining an input current, and a plurality of control inputs coupled to the at least-switch, the at least-switch is controlled in response to a plurality of control signals supplied by the charge controller The control inputs a voltage to control the voltage and current at the output of the charger, and the charge controller is configured to respond to the input voltage and the input current in a manner that approximately maximizes the electrical power acquired at the input To generate such control signals. Another feature of the present invention is a charging system comprising: an adapter for converting AC electrical power into DC electrical power, wherein when the DC current generated by the adapter is increased above a rated current value, The DC voltage generated by the adapter drops rapidly; an electronic device having a power wheel, the power input is coupled to at least one rechargeable power source and coupled to at least one circuit for defining a system load; And a charging control unit having: an input coupled to the adapter; an output coupled to the power input of the electronic device; a sensor for sensing 201251269 The DC current generated by the adapter generates a current sense signal 'and a switching circuit that is coupled between the charge control unit input and output and responsive to the plurality of control signals generated by the charge control unit 'to supply the DC voltage and the DC current from the adapter to the charging control unit in a controllable manner, the charging control unit being required by the electronic device The control signal is generated in response to the DC voltage generated by the adapter when the DC current exceeds the rated current and in response to the current signal to approximately maximize the DC electrical power generated by the adapter. Yet another feature is a method of supplying DC electrical power from an adapter to an electronic device that converts AC; current and voltage into DC current and voltage, wherein when generated by the adapter When the dc current is raised above a rated current value, the DC voltage generated by the adapter drops rapidly. The method includes: monitoring one of a DC voltage and a DC current generated by the AC adapter. And, in the event that a monitored DC voltage drops below a predefined voltage and the monitored current exceeds one of the rated currents, to approximately maximize the DC power supplied by the adapter To adaptively control the level of at least one of a DC voltage and a DC current supplied to the electronic device by the adapter. [Embodiment] Referring now to FIG. 1 ' is a functional block diagram of a charging system 201251269 1 具有 having adaptive power management including maximum power point tracking according to an embodiment of the present invention. The charging system 1 includes a charging control unit 2, which supplies a DC voltage Vout and a current Iout generated by an external power source to one or both of a rechargeable power source and an electronic system or device in a controllable manner. By. The external power source is provided in the form of a conventional Ac-adapter 16 that converts alternating current (AC) current and voltage supplied by an AC power source 18 into a direct current I0A and a DC voltage vOA. The DC voltage V0A and the current I 〇 A are "input" to the charge control unit 12 and thus may be referred to as input voltage and current in the present description, and the corresponding power (ie, P 〇 A = VOAxIOA) It will be called input power. Similarly, the Dc voltage vOUT and the current ιουτ are supplied or "output" from the charge control unit 12, and thus may be referred to as input current and voltage in this specification. An input node 24 of the charging control unit 12 receives the dc voltage V0A and the current I〇A', and the DC voltage V〇UT and current Ι〇υτ are supplied to an output node 26 of the charging control unit. As seen in Figure ι. The AC power source 18 is a conventional residential or commercial electrical installation, or a conventional power generator, and the like. In the embodiment, the charging control unit 12 is implemented (that is, placed in) an electronic device u; however, in other embodiments, the charging control unit 12 may also be associated with the electronic device. 14 is separated, that is, the spear is placed in a manner that the electronic device f 14 is separated and/or remote from the electronic device 14. For example, the electronic device 14 is a portable electronic device, such as a laptop or a notebook computer, a tablet or other tablet device, a handheld electronic device, a cellular or smart phone, and the like. Things. In an alternate embodiment, the electronic device 14 may be a non-playable electronic 8 201251269 device. The electronic device w+_device 14 includes one or more electrical circuits and/or subsystems that consume electrical energy, and in FIG. 1, such electrical circuits or subsystems are loaded with a single system 20 ± to indicate. Therefore, the system load 20 is equivalent to electricity

Subcircuit system, for example, «Ε 4m. -V Μ MA* A ·", page not stolen, touch screen, wireless network (for example 'AV i - FI) And so on, the electronic device 14 containing the system load is a smart phone, a tablet, a laptop, or other similar portable electronic device. The electronic device 14 further includes a rechargeable power source 22, which may or may include - or a plurality of conventional rechargeable batteries, one or more capacitors, and the like, in operation, the AC adapter 16 will provide The charge control unit 12 should be applied to the DC voltage v〇A and the current ι0, and then the charge control unit το 12 can be actuated from where it is generated to be supplied to the system load 2 and supplied to the chargeable if necessary. The DC voltage V 〇 A of the power source 22 and the current I 〇 A. An input node 24 of the charge control unit 12 receives the input electrical waste I and the electrical train I 〇 a ' which are also shown in Figure 1 as the input voltage v 丨丨 n and the input current IiN. When the AC adapter 16 and the charging control unit 12 are decoupled, the beta rechargeable power source 22 supplies the DC voltage V0lJT and DC current Ιουτ required by the system load 20 through the diode D i . The «Hai charging control unit 12 includes an adaptive charging controller 28 and a DC to DC converter 29. In the embodiment of Fig. 1, the DC to DC converter 29 is a buck converter (i.e., has a buck converter topology) and includes switches Si and S2 having a power M〇s transistor type. An inductor L and a capacitor c. The adaptive charging controller 28 supplies complementary pulse width modulation control signals pwMi and pWMV to the switch S 1 such as 201251269. The operation of the buck-DC to DC converter 29 is well known to those skilled in the art, and therefore, for the sake of brevity and avoidance of confusing the embodiments of the invention described herein, this operation will now be only briefly described. In operation, the adaptive charge controller 28 generates the complementary pulse width modulation control signals PWMI and PWMV for alternately turning the switches 81 and S2 on and off to produce a desired output voltage V. ^. The control signals PWMI and PWMV are complementary, so that the switches S1 and S2e are operated in a complementary manner. The meaning is that when the control signal pwMi turns on the switch si, then the control signal PWMV turns off the switch s2; Ground, when the control signal PWMI turns off the switch S1, then the control signal PWMV will turn on the switch S2. The control signals pwMi and PWMV are pulse width modulation signals which control the converter 29 for generating the desired output voltage applied to the system load 20. When the switch S1 is turned ON, energy is stored in the inductor L and supplied to the load 20. Conversely, when the switch s 1 is turned off (turned 0FF) and the switch S2 is turned on, the inductor [is coupled via the switch S2 across the load and is stored in the inductor L It will be transferred to the load 20. The PWMI signals and the pWMV signals have an associated period T, and the duty cycle D of these signals determines the value of the output voltage v0UT, and those skilled in the art will understand that the duty cycle is defined as The duration of the switch S1 is turned on (T0N) divided by the period T (D = T0N /T).

The adaptive charging controller 28 will sense a number of different signals and use the sensed signals to control the generated control signals pwMI 10 201251269 and the duty cycle D of the PWMV to generate the desired The output voltage ν〇υτ and the current Ιουτ «The charging control unit 12 further includes an input current sensor ' configured by an input current sensing resistor r1n and a differential amplifier 3A for sensing the charging control unit 12 The input current Iin, and please note that 'as seen in Figure 1, the input current I1N is also the output current I 〇 A provided by the AC adapter 16. The output of the differential amplifier 3A is a voltage VlIN which has a value proportional to the input current IIN. The charge control unit 12 also senses the input voltage ViN. In an alternative embodiment, one or more other conventional current and/or voltage sensors may be used to determine the input current IIN and the input voltage V1. The charging control unit 12 further includes a resistor. An output current sensor composed of a differential amplifier 32 and a scale amplifier 1; The output of amplifier 32 is voltage VIOUT which is proportional to the output current ι 〇υ τ supplied by charge control unit 12. In an alternate embodiment, one or more other conventional current and/or voltage sensors may be used to determine the voltage ν 〇υ τ of the output current 1 该 of the charge control unit 12, respectively. In any case, the charge control unit 12 senses the input voltage V 丨Ν and the input current Im and the output voltage ν 〇υ τ and the output current. In the embodiment of FIG. 1, the charge control unit 12 also controls a power metal oxide semiconductor (M〇s) transistor τ for limiting the charging to the power source when the rechargeable power source 22 is nearly fully discharged. Current [a flow. When the voltage of the rechargeable power source 22 is very low (that is, when the rechargeable power source is nearly fully discharged), the charging control unit 12 controls the transistor T in a linear mode such that it has an output voltage VOUT thereon. The charging current Ich captured by the output node does not cause the output voltage to drop or "Step 201251269 drops" too much. When the voltage on the rechargeable power source 22 increases to a level closer to the value of the output voltage ( For example, when the voltage of the rechargeable power supply spoon is increased to about 75 of its operational value, the charging control unit 12 will turn on the transistor T-eight-hook 70 king to allow for maximum recharging current

Ich is used to charge the rechargeable power source 22. In the embodiment of FIG. 1, the Dc to Dc converter 29 has a buck converter topology; however, other embodiments may be utilized in other embodiments, in an alternative embodiment of the present invention, The DC to, the converter has a buck-boost topology, a boost topology, or a topology, or a topology. Those skilled in the art in this alternative embodiment will appreciate that the adaptive charge controller 28 will operate to generate the control signals needed to control the operation of the DC to DC converter 29.

[OUT See the diagram shown in Figure 2, a more detailed functional block diagram of the adaptive charge controller 28 of Figure 1. In the embodiment shown in FIG. 2, the adaptive charge controller 28 includes a pulse width modulation (pWM) controller 4 that receives a plurality of control signals from a plurality of mode control modules 42 to 5G. And generating the pulse width modulation control signals pwMI and pwMv for controlling the generated output current ^ and the output voltage v0UT supplied by the charging control unit 12. The PWM controller 4 also generates a control signal PWMC' for controlling the operation of the transistor, thereby controlling the amount or the amount of the output current that is supplied as the charging current Ich flowing to the rechargeable power source 22. More specifically, the charging current is limited when the voltage on the rechargeable power source approaches full discharge. In the embodiment shown in the figures, the mode control modules 42 to 50 12 201251269 include: a constant voltage (CV) control module 42, a constant current (cc) control module 44, and trickle charging (TRjckle_charge, TR) a control module 46, a Static-Power-Management (SPPM) control module 48, and a controlled charging rate (ie, "flow-out") to charge the control signal PWMI of the rechargeable source 22 , PWMV.

The source voltage is greater than the correct power supply to the system load. 2 The adaptive power management (APM) control module 50. The adaptive charge controller 28 operates in a plurality of different modes, each of which corresponds to and is subject to Controlling a different mode control module of the mode control modules 42 to 5 . Those skilled in the art will appreciate the operation of a DC to Dc converter in each of the constant voltage cv mode, the set current cc mode 1 stream TR mode, and the static power management (SPPM) mode, thus For the sake of simplicity, it will not be described in detail in this article. Briefly, the cv control module 42 controls the operation of the PWM controller 4〇 such that the PWM signals PWMI, PWMV cause the charging control unit 12 to generate the output current at a constant output voltage v0UT. Ι〇υτ. The cc control module 44 controls the operation of the PWM controller 40 such that the control signals PWMI, PWMV cause the charge control unit & 12 to generate a strange output current W. The thirst charging TR control mode 'group 46 controls the operation of the controller 40 to cause the charging control unit 12 to sneak and sag." The minimum required for the technology to cross the rechargeable electrical load 20 is 13 201251269. The critical value - Γ | Λ π charging power supply 22 is connected to the output node 26 (Fig. 。). The 'type of the rechargeable power supply 22 will supply a part of the output current Ιουτ and if the right output current Ι〇υτ occurs in the system load 20 increases to the amount that the AC adapter 16 can supply The particular type of transient condition (i.e., greater than the input current ΙΙΝ), then the rechargeable power source 22 and the Ac Adapter 6 operate in conjunction to supply the necessary output current. The rechargeable power source is isolated from the output node 26 when the voltage across the rechargeable power source 22 is less than the minimum threshold required to properly power the system load 2 (Fig. 透过 and through the scale control module 46 is charged in the "turbulent" mode. When the specific operating conditions of the input voltage V1N and the input current I1N are present, the control module 50 controls the pwm controller 40 for generating the control signals PWMI, PWMV. More specifically, the ΜρΜ control module 50 controls the PWM controller 40 in the APM mode when the input voltage VlN falls below a voltage threshold or when the input current I IN exceeds a current threshold. This will be explained in more detail below. For example, when the output current Ιουτ required for the combination of the system load 20 and the rechargeable power source 2 2 exceeds the input current I1N that can be taken from the AC adapter 16 ( That is, the required input current I1N exceeds the maximum output current I 〇 A that can be supplied by the AC adapter 16. This is true. Those skilled in the art will understand the 'input voltage VIN. This drop in the middle indicates that the input current I1N has become very large' such that the input voltage has begun to "crash".

Figure 3 is a more detailed functional block diagram of one of the embodiments of the APM control module 5A of Figure 2. In the embodiment shown in the figures, the APM 201251269 control module 50 includes a maximum power point tracking (mppt) module 52 that receives an input voltage VlN (Fig. 1) and an input current signal VnN (Fig. 1). As described in more detail below, the ΜΡΡΤ module 52 is operable to generate a reference control signal Vr in response to the wheeling voltage Vin and the input current ΙΙΝ. The input dynamic power management (IDPM) control module 54 can respond to the reference control signal Vr and to one or more of the output current signal VIOUT and the output voltage νουτ in a conventional manner. The PWM controller 40 (FIG. 2) is controlled to generate control signals PWMI, PWMV, and PWMC such that the output current 1〇1]7 is preferentially sent to the system load 20 and the remaining output current Ι〇υτ is treated as The charging current Ich is used to charge the rechargeable power source 22. Those skilled in the art will appreciate that the IDPM control module 54 is also operative to reduce the input current Iin in response to the input voltage v1N dropping below a threshold VINDpM, thereby preventing the input voltage from dropping further. 4 is a block diagram of one embodiment of the MPPT module 52 of FIG. In the embodiment shown in the figures, the MPPT module 52 includes a comparator 58, one of which receives the input voltage Vin and the other input receives an input threshold VE»the input threshold γΕ The output voltage v0A of the AC adapter 16 (圊1), which in the foregoing discussion is the input voltage V1N of the charge control unit 12 of FIG. Therefore, the comparator 58 determines whether the input voltage vIN has fallen below the input threshold VE; as also discussed above, when the output voltage V〇a of the AC adapter 16 (ie, the 'input voltage VlN' has decreased) By the time the input threshold vE is below, the IDPM control module 54 (Fig. 3) will be activated. 15 201251269 The comparator 58 shown in the figure will be designed to have a specific amount of hysteresis such that the comparator 58 will be at the input voltage Vin (i.e., the output voltage V〇A from the AC adapter 16). When it falls below the input threshold value Ve, a functioning enable signal E is generated; conversely, when the input voltage V... rises to be greater than the sum of the input threshold value vE and the hysteresis voltage Vh"(V1N>VE When + VH), the comparator 58 generates an inactive signal E. Alternatively, the comparator 58 may be configured to generate a useful enable signal E when the input current signal V11N indicating the value of the input current 1^ rises above the input threshold VE; and at the input When the current signal vIIN drops to a voltage smaller than the difference between the input threshold value Ve and the hysteresis voltage vh, the enable signal E is driven to be inactive. In this case, the input threshold vE is related to the hysteresis voltage Vh and the current threshold associated with the current I 〇 A / Iin from the Ac Adapter 16; in the former case, both are associated with the AC The output voltage of the adapter, v〇A, is related to the voltage threshold. The MPPT module 52 further includes an adaptive gain and chopper circuit 60 that receives the input voltage VH at one of the inputs (i.e., corresponds to the output voltage of the AC adapter 16) and generates Once the adjusted voltage vA is used as the output β, the adjusted voltage Va is provided to one of the analog-to-digital converter (ADC) circuits 62. Another adaptive gain and filter circuit 64 receives the input current signal v11N at one of the inputs (i.e., the value corresponds to the voltage signal of the output current I 〇 A of the Ac Adapter 16) and produces an adjusted The current signal Via is used as an output, and in the figure, a value corresponds to the voltage signal 16 201251269 of the output current of the AC adapter 16 adjusted by the adaptive gain and filter circuit 64. The adjusted current signal VIA is provided to the other input of the adc circuit 62. The ADC circuit 62 can be operated in a conventional manner for converting the adjusted analog signals VA and Via into corresponding digital signals Vad and ViAD 'which will be known for separate outputs on the ADC circuit 62. . The yAD output of the 5H ADC circuit 62 is then provided to one of the inputs of a conventional digital multiplier circuit 66 and is also provided to the other input of the adaptive gain and chopper circuit 60. The VIAD output of the ADC circuit 62 is provided to the other input of the digital multiplier circuit 66 and is also provided to the other input of the adaptive gain and filter circuit 64. In one illustrative embodiment, the ADC circuit 62 is a 10-bit analog to digital converter, so the total count range is 1024 (for example, '21Q); however, the ADC circuit may have more Or the resolution of fewer bits. The ADC circuit 62 receives the enable signal E generated by the comparator 58. Therefore, the ADC circuit 62 is operable to operate when the enable signal e is activated (for example, 'when the input voltage V1N is used) The analog signal vA, VlA is converted into a digital signal when it is sufficiently smaller than the value of the threshold VE or when the value of the input current IIN is sufficiently larger than the value of the threshold VE. Conversely, when the enable signal E is cancelled (for example, when the value of the input voltage vIN is sufficiently larger than the value of vE or when the value of the input current iin is sufficiently smaller than the value of VE), the ADC circuit 62 will be disabled and thus cannot convert these analog signals VA, VIA. In such cases, the output of the APM control module 50 (Fig. 3) does not affect the operation of the adaptive charge controller 28 (Fig. 1); since the adaptive charge controller is operated in this case 17 201251269 It is in a mode controlled by one of the other control modules 42 to 48 (Fig. 2). The output of the ADC circuit 62 may thus be set to a predetermined value, which may cause the output Vr from the Μρρτ module 52 to have no effect on the operation of the control module 54 and/or Or it may cause the rotation of the IDPM control module 54 to have no effect on the operation of the adaptive charge controller 28. Each adaptive gain and filter portion of the filter circuit 6〇, 所示 shown in the figure is provided to remove noise that may appear on the analog input signals VIN and VnN. In this regard, each of the adaptive gain and chopper circuits 60, 64 is a conventional low pass filter in one of the embodiments of the ΜΡΡΤ module 52. In other embodiments, the adaptive gain and chopper circuits 60, 64 may be other known types of signal filtering circuits. The filtered analog signals Vin and VnN may be referred to herein as f(vin) and f(viin)', respectively, and correspond to the filtered analogy of the circuits 6〇, 64 before applying the gain to the signals. Signal. Each of the adaptive gain and adaptive gain portions of the filter circuits 60, 64 shown in the figure are configured to apply to the filtered analog input signals f(vin) and F(VlIN) (for example Saying 'as a multiplier' adaptively determines the gain so that each generated analog signal and V1A value will fall within a window defined by previously defined low and high values. For the purpose of interpreting the operation of the adaptive gain and filter circuits 60, 64, the gain applied by the adaptive gain and filter circuit 6 to the filtered analog signal F(Vin) is denoted herein as G6. 〇, and the gain of the adaptive gain and waver circuit 64 applied to the chopped analog signal 18 201251269 f(v„n) is denoted herein as G“. Therefore, according to these expressions ' VA = g60 * F (VIN) and ν ΙΑ = G64 * f (viin). Each of the adaptive gain and filter circuits 60, 64 shown in the figures is designed to compare the individual outputs of the ADC circuit 62 with the previously defined low and high values and to The value of the individual output of the adc circuit 62 is greater than the previously defined high value and the value of the gain is reduced and the value used to increase the gain if the value of the individual output of the g ADC circuit 62 is less than the previously defined low value. It should be understood that the low or high values of the adaptive gain and money circuit 6() may or may be the same for the adaptive gain and data circuit 64. The values are the same as or different from the high values, and ^ various. Implementation of the financial, you can choose the same value of the square wire to select these low value. The system that should be further understood that 'these circuits 6Q, 64 may be configured to increase or decrease the amount of their individual gain values that are the same or different' and that in each circuit, the amount of gain that is increased may be Same or not the same as the amount of the reduced gain. In the application of the different embodiments of the Μρρτ modeling η, either or both of the circuits 6〇, 64 increase and/or decrease the amount of their individual gain values and may be the same/the same adaptive gain In the interpretative example of the filter circuit portion, the previously defined low value of the adaptive gain liver (four) rail circuit 60, 64 per power 64 is the full neighbor of the ADC circuit 62. 25% of the range of the P-P (that is, the maximum count value of the ADC circuit 02), the high value of the value to the mother circuits 60, 64 is 75% of the full range of the ADC circuit 62, and , - a gain value of G6. The amount that is increased or decreased with G64 is 1/2 of the current gain of 19 201251269. Taking the ADC circuit 62 of the M-ary as an example, the entire range of the circuit 62 is 1〇24. Therefore, the previously defined low value is 7·25*1〇24)=256' and the high value defined in advance is defined. ((.75*1G24)=768. In this exemplary implementation of the adaptive gain (4), wave H circuits 60, 64, each of the circuits 6Q, 64 will thus be in the same manner by comparing the counts of ^ and V1A with 256 and 768, respectively. If the count value of the operation mA is less than 256, then the gain value ' will be doubled (for example, g60=2*G6.); and if the count value of ~ is less than 256, then the gain value G will be the same. It will be doubled (for example, G64=2*G64). Instead, if the count of Va is greater than 768, then the gain value Gw will be halved (for example, ' =(}6〇/2 And if the count value is greater than 768, then the gain value & will also be halved (for example, g64 = G64/2). Instead, if the count value VA or ViA is between 256 and 768 If so, then the corresponding gain values Gw or Gw will not change. This process will continue until V1A is between the previously defined low and high values (for example, 256 and 768). Between the two. It should be understood that this special implementation is only provided as an example, not This is considered to be limiting. The digital multiplier circuit 66 is operable to multiply the digital signals Vad and Vmd from the ADC circuit 62 to generate an input power PIN = VAD * V1AD ' The electrical power received by the charging control unit 12 (i.e., the electrical power input power PIN provided by the AC adapter 16 of FIG. 1) is provided to a storage and comparison circuit 68 that contains one or more memories. The register (not shown in Figure 4) stores the most recent value of the 4-input power PIN in the memory registers 20 201251269. The store and compare circuit 68 further compares the current value of the input power Pin. And the previously stored value of the input power pm. The storage and comparison circuit 68 also uses the input power

The step value is determined based on the difference between the current value of Pm and the stored value, and the direction of the input power is determined based on whether the current value of pIN is greater than or less than the stored value of the PIN. value. The step value decision may or may not be weighted and may be a simple arithmetic difference calculation or include one or more complex difference decisions. The store and compare circuit 68 uses the step values and direction values to produce an output that is provided to a conventional digital to analog converter (DAC) circuit 70 which converts the sigma output to the Refer to a current value of the control signal Vr. The IDPM control module 54 of FIG. 3 is operable to apply a control signal to the pWM controller 40 (FIG. 2) in response to a reference control signal VRffi from the DAC circuit 70, which will then be as previously described. Control the duty cycle of these control signals PWMI, PWMV. The APM control module will depend on the electrical power required by the system load 20 or the electrical power required by the combination of the system load 20 and the rechargeable power source 22 to be greater than the electrical power that the AC adapter 16 can generate. This mode operates to control one or the other of the input voltage VIN and the input current I1N such that the input power (Fig. 1) supplied from the AC adapter 16 to the charge control unit 12 is maximized. The value 'will be explained in more detail below. In one embodiment of the present invention, the storage and comparison circuit 68 of the MPPT module 52 of FIG. 4 determines the step value according to one or more conventional input power maximum 201251269 algorithm. In one embodiment, the store and compare circuit 68 is configured to determine the step value using a conventional maximum power point tracking (MPPT) algorithm, which is designed to be used to Adjusting the reference control signal VR to a maximum maximizes the value of the input power pIN supplied by the ac adapter 16. For example, the Μρρτ module 52 may perform a Μρρτ algorithm in the form of a conventional perturb-and-observe method. In this manner, the MPPT module 52 adjusts the value of the reference control signal Vr from its current value to a new value, and then determines whether the new reference control signal value causes the input power Pin to increase or decrease. . If the input power P1N is increased, then the Μρρτ module 52 will adjust the Vr signal again in the same direction (for example, the value of the VR condition number is increased by the step value again. Next, the Μρρτ Module a will again judge _ this new reference control number value causes the input power p1N to increase or decrease. As long as the input power Pin increases, then the MPPT module 52 will continue to increase in this way. The method of adjusting the vR signal. When the MPPT module 52 determines that the new value of the reference control signal causes the current input power & lower from its previous value, then the MPPT module 52 will be in the opposite direction. Increasing the % signal in the middle. For example, if the value of the A signal is increased by the step value and the value of the A signal is increased, the Μρρτ module will continue in this way until the At the point where the input power drops, the MPPT means && the group will reduce the Vr signal by the step value. At this point, each of the #3, 3 has the APM mode of the MPPT module 52. Group 50 positive 22 201251269 In controlling the charging system 1 图 (Fig. i), therefore, the charging system is at the maximum power of the AC adapter 16, or more precisely at the maximum power of the AC adapter 16 The operation will be explained in more detail below with reference to Figures 7a and 7B. Referring briefly to Figures 7A and 7B, it will be seen in these diagrams that in the APM mode of operation just described, the input voltage Vin and the input current Iin The value will be slightly changed or "dither" with a specific intermediate value corresponding to the true value of VIN and IlN that causes the maximum output power of the AC adapter 丨6. This is true because The Μρρτ module 52 uses the step value to adjust the Vr signal, and the finite step value causes the input voltage VlN and the input current Iin to be centered on the true maximum power of the AC adapter 16 or Flutter, and thus the chattering of the input power PIN. The δ 玄 MPPT module 52 will eventually reach a point when a given step value change causes the input power ΡΙΝ to decrease, and the Μρρτ module will then change to join the step The order value is used to adjust the direction of the v R signal. For example, it is assumed that continuously increasing the Vr signal by the step value causes the input power Pin to have a continuously increasing value. At a specific time point, the new incremented Vr signal This will cause the input power Pin to drop. The MPPT module 52 will then change the direction of adjustment of the VR signal, and thus decrement the Vr signal by the step value. This will cause the input power plN to increase '俾 such that the Μρρτ The module 52 will decrement the Vr signal again. This time, the input power p1N will be lowered. Therefore, the MPPT module 52 will change the adjustment direction of the Vr signal again and pass the Vr signal by the step value. The Μρρτ module 52 will continue to operate in this manner to control the charging system 1〇 such that the wheeling power p1N supplied by the AC adapter 16 23 201251269 will change or tremble around the true maximum. To reduce the amount of this flutter, the MPPT module 52 will reduce the magnitude of the step value when detecting the dither condition and thus control the charging system 10 to be closer to the authenticity of the AC adapter 16. Maximum power PiN. Other embodiments of MPPT module 52 may employ different Μρρτ algorithms: for example, conventional incremental conductance, constant voltage, go, or the like. Moreover, in other embodiments, the storage and comparison circuit 68 in the bribe module 52 may be operated in an alternative manner to determine the step value according to other conventional maximum decision techniques. Examples include However, it is not limited to one or more numerical search techniques, one or more conventional iterative techniques, or the like. The MPPT module 52 further includes a power saving circuit 72 that receives the reference control power M VR and is operable to generate an enable signal en, which is applied to the device 6〇7 7 Hey. This signal places the devices 60 to 7G in a low power or standby mode of operation and thus places the MPPT module 52 in a low power or standby mode of operation as will be described in more detail below. What is not shown in Fig. 5 is the timing circle of the 胄4 丁 命 命 。 根据 根据 according to one of the embodiments. It should be understood that the timing diagram shown in FIG. 5 is the reference control signal generated by the MPPT module 52 and should be understood. The remaining timing waveforms of the figure + μ + > ' represent the operation period. Among the MPPT modules, the funds were collected from the events of Ji Guanying. Figure 5 is arranged in this manner to display the timing of the event of the MPPT module 52 >上吐> 相对 relative to the final change in the value of the reference control system VR Explain (4) the power saving features implemented in the adaptive 24 201251269 charge controller 28. In this regard, the low level to high level (or high level to low level) transitions in the CLOCK timing waveform 86 represent the starting point of each complete event group performed by the MPPT module 52. A complete set of events executed by the MPPT module 52 is illustrated in FIG. 5 by a combination of a Vr signal 98 and a plurality of event waveforms, including: MEASURE waveform 87, c〇mpare waveform 90, ADJUST The GAIN waveform 92, the Measure & st〇re waveform 94, and the ADJUST waveform 96, and the horizontal axis represents time t. For example, the first complete event group begins at time t〇, where both the CLOCK timing waveform 86 and the MEASuRE waveform 87 transition from a low level to a high level, which will signal a separate measurement (for example, The input voltage Vin and the input current V丨丨N are performed by the adaptive gain and filter circuits 6A and 64. In the duration of the MEASURE waveform 87, v

V IN and VnN will be transmitted through the adaptive gain and filter circuits 6 〇 , 64 '俾 such that V 〖N and V „N will be filtered separately and then multiplied by the corresponding gain value (for example, multiplied by Gw and Gw, both set to 1) on the first pass, the ADC circuit 62 converts the generated VA to Vad and Via to VIAD, and the digital multiplier 66 then calculates piN. As described above, at time t1, the MEASURE waveform 87 will transition from a high level to a low level and the COMPARE waveform 90 will transition from a low level to a high level during which the store and compare circuit 68 will compare pw and The previous value of Pin stored in one or more memory registers of the store and compare circuit 68 is used to determine the step value and the direction of change of the VR as described above. In the first event group For example, piN's 25 201251269 stored value may be, but not limited to, the previously stored Pin value 'default power value, or the current value of pIN. Then, at time, COMPARE waveform 90 will Switch from high level to low level and adjust G The AIN waveform 92 will transition from a low level to a high level during which the adaptive gain and filter circuits 60 and 64 will adjust the (equal) gain values Gw and/or gm as necessary, as described above. At time t3, the ADJUST GAIN waveform 92 will transition from a high level to a low level and MEASURE & STORE will transition from a low level to a high level during which the 4 adaptive gain and filter circuits 60 and 64 will measure separately. The input voltage Vin and the input current V„N, and V„N are transmitted through the adaptive gain and filter circuits 60, 64 such that Vin and Viin are respectively filtered and then multiplied by corresponding (and possibly The adjusted gain values Gw and Gw, the ADC circuit 62 then converts the generated Va to VAD and converts the vIA to Viad, and the digital multiplier 66 then calculates the PIN' and the store and compare circuit 68 proceeds. The current Pm and previous values stored in one or more memory registers of the store and compare circuit 68 are compared to determine the step value and the direction of change of Vr. Then, at time U , MEASURE&amp The STORE waveform 94 will transition from a high level to a low level and the ADJUST waveform 96 will transition from a low level to a high level ' during this period'. The DAC circuit 70 will convert the step value and direction into an analog signal, for example, The voltage signal in the example, and this voltage signal is added to the current value of VR, which will then change the response of vR 98. In the example shown in Figure 5, VR 98 will be at time t4 to t5. A change in the value of the increase in duration (for example, the amount of increase Δ 26 201251269 v) occurs. At time t5, Vr 98 has been adjusted (i.e., ΔV has been increased), and therefore, ADJUST waveform 96 will transition to a low level at a high level. As mentioned in the face, in order to reduce the amount of the face vibration, the MPPT module 52 will reduce the size of the step value at a specific time point corresponding to Δv in FIG. 5 during the operation. . Time k will end the first complete event group executed by the MPPT module 52. Referring again to Figure 4, the Μρρτ module 52 further includes a power saving circuit 72' in the figure which receives the reference control voltage % as input and produces a uniform energy signal ENf as an output. The enable signal en is provided to the enable inputs of the adaptive gain circuits 6A, 64, the adc 62, the multiplier circuit 66, the store and compare circuit 68, and each of the μ. As shown in the figure, + less + & Μ ... Hai, the electrical circuit 72 will monitor the reference control voltage vR, and during ti / t4, that is, when 胄 is adjusted, the enable ^ 1 ^ ^ 1...Only N will be set to - operation enable value, for example, logic two or logic low] W material circuit 6 〇, 62, 64, 66, 68 material ^. Module AX, + 8, and 7〇 are completely optional. When the VR is displayed during the ADJUST time period (for example, between _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ For example, the 'change to logic low level or variable (10) value' is set to - circuit disable value. In the figure, it is used to finance the ,, the circuits 60, 62·6 are given the actual circuit disable value of the module 52 to enter the standby mode, and 70 will respond to the circuit 60. , 62, 64, to; "Z. As shown in the figure, the standby mode of 66 and 66 is the shutdown mode, where 27 201251269 these circuits 60, 62, 64, and 66 will completely turn off the power, so they do not consume any current. The standby modes of circuits 68 and 7 shown in the figure are sleep modes in which they only consume enough current to maintain the Q method (i.e., stored and current) data. Therefore, for example, the power saving circuit 72 may turn off or disable some or all of the Mpp module 52 during the time interval ts to t0 in response to a value of the value or a stable value. The electrical power of the remaining circuits disables the Μρρτ module 52, thereby conserving power during this time interval. After a predefined waiting time period (i.e., between and te), the power saving circuit 72 changes the value of EN again, for example, to a logic high level or a logic low level. At time t6, EN is reset to the circuit enable value. Time t6 will begin a new complete event performed by the MPP module 52, and the event will restart between time h and t0 and be executed between times u and tll, and As long as the Μρρτ module 52 is activated, it will be repeated later. Of course, at a certain point in time, when the reference control signal vR is given a change in the step value Δν to cause the input power to decrease, as discussed above, the value of the reference control signal will be lowered. The order value is ΔV, not increased. Figure 6 is performed by the module Μ and IDPM control module 54 in the ΑΡΜ control module and the pwM controller 4 of Figure 2 for maximizing transfer by ac under the operating conditions described above. A flowchart of one of the explanatory powers of the power generated by the device, in other words, the input current IIN required for the combination of the system load 20 and the rechargeable power source 22 exceeds the AC adapter 16 The current that can be supplied. In one of the explanations 28 201251269, in the embodiment, the MPPT module 52 is implemented in the form of a pure analog circuit system, and in this embodiment, FIG. 6 is not in the G. The method 100 represents an algorithm performed by such a specific circuit system. In embodiments that may include _ or a plurality of conventional processor circuits (for example, - or a plurality of microprocessors, signal processors, or the like), the method may be at least partially- Or in the form of a plurality of software algorithms, which are stored in-memory and executable by the processor circuit to at least partially implement the method 100. For purposes of illustration, the method 1 described herein is performed by the PWM controller 40 of the MPPT module 52 2 to the IDPM control module 54, and the map is executed and executed. The method (10) starts from step 1G2, at which the MPPT module 52 monitors the input voltage Vin and monitors the input current through the signal v(10), which corresponds to the output voltage V〇A generated by the AC adapter 16 and Output current IOA (I〇A=IlN). Then, at step 1〇4, the MPPTI group 52 determines whether the input voltage ViN is less than the input threshold νΕ1, or 'in an alternative embodiment, it is determined whether Vi丨N is greater than another predefined voltage value VE2. Used in the context of the description of the method

The input threshold value Ve above which is above β is the threshold value of the input voltage Vin or the voltage ^ from the adapter 16, and is represented by Vei in this case. Alternatively, the input threshold value Ve is the input current Im or the critical value of the current I 〇 A from the ac adapter 16 and is represented by γη in this case. The input threshold value νΕ1 is the value or magnitude of the output generated by the Ac adapter 16 = the pressure V0A. Those skilled in the art will understand that 'when the output current is less than the rated current of the adapter, the output voltage V The phase chargeable power source 22 of the output voltage V〇A of 201251269 is desirably sufficiently below the constant magnitude produced by the AC adapter 16. The system load 20 and the desired current I 〇 A (i.e., the input current I1N) exceed the current that the AC adapter 16 can provide. In the exemplary embodiment where the relatively constant value of v0A is typically 5 volts volts, for example, Vei may be set to 4 75 volts; however, the invention also covers other values of VE1. In the embodiment where the reference control signal is v1R, Ve2 shown in the figure corresponds to the value or magnitude of the output current I0A generated by the AC switch H sufficiently above the rated current to indicate the charging control unit 12 The output current I 〇 A required for the combination with the system load 20 or the combination of the charging control unit 12, the system load 20, and the rechargeable power source 22 requires a larger output current I 〇 A than the AC rpm. The current that the connector 16 can generate. In either case, the branch line "No (n〇)" of step 1〇4 will cause the method to return to step 102; and the branch line "yes" of step 1〇4 will proceed to step 106, where Wherein, the Μρρτ module 52 is operable to calculate the wheeling power Pin by a well-known function of v_ and vIN, for example, pIN-K*v"N*VlN, where the κ-system is set to be converted to h The constant of the true value. Of course, the wheeling power PIN is the output power generated by the AC adapter 16, and step 1〇6 will go to step i, where the MPPT module 52, the IDPM control module M, and the pWM controller 4〇 Will work together to adaptively modify VnN and/or Vin to maximize Pin, as discussed above with reference to Circles 3 through 5. Then, at step u, the MPPT module 52 is operable to wait for a predetermined period of time, and during this waiting period, by having all or most of the circuits of the internal 30ρρτ module 52 internal 30 201251269 The system stops and saves the waiting period of the step 110 of the gt; τ module 52. The MPPT module 52 consumes little electric power, and even does not eliminate any electric power, and the electric power is saved when the ... 7 module does not need to operate. . Then, at step 112, the MPPT module 52 is operable to compare VIN and 'or' to compare VII_VE2_VH2, where VH1 and VH2 represent previously defined hysteresis voltage values. Therefore, if the health VIN does not increase at least VH1 above VE1 (or, if VUN does not fall below at least VE2), the party *(10) will loop back to step 106. Otherwise cough method, will loop back to step 1G2, restart the method just. It should be understood that 2' whether the reference control signal is ^, any of the ~ and ^ or both can be estimated to determine whether the party 4 should just proceed from step 104 to step, step 106, that is The Μρρτ module 52 is activated; and/or used to determine whether the method 100 should leave steps "6 and (10), that is, '#cancel or interrupt the operation of the Μρρτ module 52. In any case, the 'input dynamic power control module M will respond to the reference control signal ^ in a conventional manner to generate a control signal. The PWM controller 4 will utilize the control. The signal is used to control the duty cycle of the control signal or the PWMV by controlling the switching source or 82 mesh to obtain the maximum available output power corresponding to the ac adapter 16 from the AC transfer $16. The input current ~ (which corresponds to the output current w of the AC adapter 16) and the input voltage Vin (which corresponds to the output voltage v 〇 a of the AC adapter 16). In this manner, the switching circuitry of the charging control unit 12 is controlled, and the ac adapter 31 201251269 16 is capable of generating a maximum wheeling power and charging the power source 22^ and supplying to the system load 20 as may be mentioned above. The @7A and 7B are shown in the APM control of Figure 6: the input power plant generated during the method and the input current I1N; In the Am mode of operation, the input voltage % and the value of the wheeled power are dithered at a particular intermediate value corresponding to the true value of v丨_^ which results in the maximum power output of the AC adapter 16. This can be seen in the APM mode of operation to the right of Figure 7A and to the left of Figure 7B. Another mode of operation is shown in Figures μ and 7B, in other words, a constant voltage π mode. As seen in these figures, during the cv mode of operation, the CV control module 42 and the PWM controller 4 as seen in Figure 2 will control the % to DC converter 29 (Fig. 在一, for a value) A constant output current Ι〇υτ' is generated at a predetermined output voltage (iv), and accordingly, the input voltage ViN and the input current IIN have a substantially constant value m brother corresponding to that seen in FIGS. 7A and 7B, The Ac Adapter 16 is capable of supplying the input power "Iin' required for the charging it 12 (Fig. 1) to supply the constant output current ιουτ and the constant output voltage ν 〇υ τ. Then, in Fig. 7A, it will be time. An event occurs at t〇. For example, the system load 2〇 (Fig. 1) requires a surge current, and the output current will exceed the current that can be supplied by the AC adapter 16. Therefore, the input voltage ViN Will "fall down" or start to fall at the time, causing the APM module 50 to start operating in the ΑΡΜ mode at time t1 after a delay time. As discussed above, the input voltage VlN and the input current ΐΝ will tremble during this mode At some later point in time, the system load 2〇 required 32 201251269 The surge current will be terminated. This can be done in this example of Figure 7B, the charge control unit. I. Therefore, 揸—· In the evening, the operator starts operating again at the cv nucleus t, which occurs at time t丨 of Figure 7B. Figure 8 is in accordance with the present invention - an embodiment, Figure 2: Charge Controller A more detailed functional diagram of the operation of 28 The charge controller 28 will switch between these different modes of operation during operation: = operation of the charge control unit U ^ Figure 8 of the formula, except for a new ^ input - current - limit control In addition to the module 8 , a CC control module 44 and a technical control module 5 are also displayed. In the case of beans, more or less control modules may be included, for example, Figure 2, heart 8 ΓΓΓ 46 and SPPM control module 48, however, the control module shown in Figure 8 will now be referred to only with reference to the figure. Figure " A member is used to determine which operating mode is preferentially controlled. The way the unit is called the operation mode of Figure 。. As seen in Figure 8, each (4) Modules 42, 44, 5G, and 80 all include a corresponding error amplification thief E/A 'which drives - a corresponding output transistor τ that is connected between ground and the common output node μ. The input _ current limit The control module (9) f includes a switch SW operative to selectively isolate the corresponding output transistor T from the common output node 82 in response to the enable signal E generated by the comparison 2 in FIG. Or the corresponding output transistor T is coupled to the common output node 82, which will be described in more detail below. Each control module 42, 44, 50, and 8〇 will receive a corresponding L boundary. Value or reference signal and __ operating parameters that are monitored or sensed. It is said that the CV control module 42 receives an output reference voltage 33 201251269 V0UT-REF and also senses the output voltage v〇ui_ CC control module 44 receives the output reference current I〇UT-REF and also senses The output current is measured; [〇υτ, ΑΡΜ control module 5〇 senses the input voltage and receives an input reference voltage V1N-REF. Finally, the input-current-limit control module 8〇 senses the input power I1N and the input reference current Iin.ref. When the input current I1N exceeds the input reference current IIN_REF, the error amplifier E/A and the control module 80 generate an output for the PWM controller 4 (FIG. 2) to control the buck converter 29 (FIG. 1) for Limiting the value of the input current and thus protecting the AC adapter 16 » As seen in Figure 8, the outputs of the error amplifiers E/A are connected to the output node in a wired-to-wire configuration 82, 俾 causes the "hardest" or the error amplifier that turns on its corresponding output transistor T in the maximum output mode to control the level of the voltage at the output node. The common output transistor 84 is controlled by the voltage at the output node 82 and is coupled in series with a constant current source between the voltage supply Vcc and ground. The interconnection of the common output transistor 84 and the strange current source 85 is defined - the comparison node 88' will be (4) coupled to - one of the inputs of the comparator 91 / the other wheel of the comparator will receive a The ramp signal or the miner signal. The comparator 91 generates a PWM output signal in response to the ramp signal and the voltage on the comparison node 88. The error amplifier E/A, which is the hardest to turn on its corresponding output transistor τ, controls the level of the voltage on the output node 82, which in turn determines the extent to which the common output transistor 84 is turned on. The extent to which the common output transistor 84 is turned on determines the (four) level on the comparison node 88. The value is 34 201251269. The current source 85 discharges the comparison node (9) at a fixed rate and thus discharges the comparison node, and the current flowing from the voltage supplier Vcc through the battery body 84 charges the comparison node. . The voltage level on the comparison node 88 is thus determined by the extent to which the transistor 84 is turned on and thus is determined by the current flowing through the transistor, and the most effort is made to turn on the error amplifier E/A of its corresponding output transistor T. The level of the voltage on the output node 82 is controlled, which in turn determines the extent to which the common output transistor 84 is turned on and thus determines the voltage level at the comparison node 88. Of course, the voltage level on the comparison node will determine the noble cycle of the PWM signal generated by (4) n 91. Now, the following examples will be explained to explain the integral joint operation of the control modules 42, 44, 5, and 80 to provide overall control of the charging system 1 of FIG. It is assumed that the rechargeable power source 22 is initially almost completely discharged, which means that the charging control unit 12 is supplying a very large output current Ιουτ, which includes a charging current Ich for charging the rechargeable power source and is supplied to the system load 20 Load current iL. In this case, the required output current Ιουτ may be greater than the input current 能够 that the AC adapter 16 can supply. Allowing the AC adapter 16 to provide this high input current Ιιν will overload the AC adapter, which may damage or damage the adapter. In this case, the input-current-limit control module 8〇 senses the extremely high input current IIN, so the control module determines the voltage level on the common output node 82, and then determines the The voltage level on node VIII is compared to control the PWM signal generated by the comparator 91. The generated PWM signal will limit the input from the AC adapter 16. 201251269 Incoming current w This input current Iin will be used to provide the required load current IL. The system is loaded with 20 ’ first and the residual current is used as the charging current IcH to charge the rechargeable mine. The sinusoidal adaptive charge controller 28 controls 曰_ |q #1: Μ Τ in Fig. 1 to set the charging current Ich to an allowable value. Now rice. Again, the system load 2 〇 and/or the rechargeable power source 22 requires less current, which means that the output current w is now relatively low. Further false - again - Hai AC adapter 16 can now supply the necessary output current [ON. In this case, the CC control module 44 may now control the entire operation, which means that the control group will drive the common output node 88 to control the voltage level on the node and control the method in this manner. The voltage level on the node 比较 is compared to control the pwM signal generated by the comparator 91. In this manner, the CC control module 44 allows the adaptive charging controller 28 to operate to supply a constant output current Ι〇υτ, a portion of which is used to charge the charging power Igh of the rechargeable power source and is used in part. The load current supplied to the system load 20 is supplied. It is now assumed that the rechargeable power source 2 2 is nearly fully charged after a period of time, which means that the required charging current IcH will thus decrease. Therefore, the required output current Ιουτ will become low, and at this point, the cv control module 42 will control to determine the voltage level on the common output node 82 and thus determine the voltage level on the comparison node 88. quasi. The cv control module 42 controls the pwM signal generated by the comparator 9 in such a manner as to maintain the output voltage ν 〇υ τ at a substantially constant value at the necessary output current ιουτ. 36 201251269 »Hai APM Module 50 will control the overall operation in the same way and in the Μρρτ mode when the input voltage drops below the corresponding reference value Vin ref and the enable signal E is active to close the switch sw Control the system ίο. When the ΜΡΡΤ mode is activated, the ΑΡΜ module 5 操作 operates as previously described to adjust the input voltage Vin and the input current 丨 ... to thereby obtain the maximum power from the AC adapter 16 . In this manner, the rechargeable power source 22 has a maximum current that can be drawn from the AC adapter 16 without causing the AC adapter to be overloaded. In the APM module 5 Μ ρρτ mode _ the entire operation of the operation, if the generated input current h exceeds the input current limit reference of the input mlong module 8G: IlN-REF, then the input The _current_limit control module will control the entire operation of the charging system H). Therefore, during the operation of the mode module A, the mine module may adjust the input voltage by attempting to maximize the power obtained from the AC adapter ι6, and thus cause the input current I1N to increase. The input current limit reference value Iin.ref of the input-current_limit control module is reached. When this occurs, the input_current-limit control module 80 controls the entire operation and the module is disabled (i.e., the enable signal E is driven to be inactive to open the Switch SW). FIG. 9 is an input current, input for operation of the adaptive charging control benefit 28 of FIG. 2 for obtaining maximum power from the adapter 16 according to one embodiment of the present invention. Diagram of voltage and wheel power. The figure also shows the corresponding power IN=vinxIin. In operation, the mine module 5q controls the adaptation of the map. 37 201251269 The charge controller 28, which bypasses the 7K fi, the charging system 10 operates at a point not shown in FIG. Ice is willing to be at this location, the AC adapter] 6 input input

M ^ is at 1"Μ at Vapm, causing the AC to supply maximum power at that point. For the purpose of comparison, figure ! ‘t other operation points Α ^ B. ‘Point Α corresponds to the operating point when the charging system modulates the current, and the system (ie, see module 8 of circle 8) operates. The point Β corresponds to the operating point at which the adapter can operate in accordance with the conventional input dynamic power management IDPM, such as #f·f+ U q AA μ on for the control module 54 of the circle 3. Point Μ, A, and B enter the relationship diagram from the agricultural D l A β system is not on the force distribution Pin ' and can be seen from the relationship diagram, the input power generated by the point μ Ριν is greater than the point eight or Β, Also, the point is the maximum power point of the Μ Adapter 16. The function of the input electric ink VIN and the input current I1N shown in the arrow "in FIG. 9" and the operation of the adaptive charging controller 28 discussed in the MPPT mode during the operation of the MPPT mode, how the V|N is rotated at the maximum power Point M is the center to produce changes and flutter. Those skilled in the art will appreciate that the various embodiments and advantages of the present invention are set forth in the foregoing description; however, the above disclosure is merely illustrative and It can be changed in the details and still fall into the broad principle of the business. For example, the above-mentioned τ ^ state pieces may be implemented by digital or analog circuits or a combination of the two. And, if appropriate, may also be present via software implemented on a suitable processing circuitry. Therefore, the invention is limited only by the scope of the accompanying claims. [Complete description of the drawings] 38 201251269 A functional block diagram of a charging system with adaptive power management in accordance with one embodiment of the present invention. Figure 2 is a more detailed functional block diagram of the adaptive charging controller of Figure i. Figure 2 is a more detailed functional block diagram of one embodiment of an adaptive power management (ApM) control module of Figure 2. Figure 4 is a diagram showing the maximum power point tracking (MPPT) mode of Figure 3, in accordance with one embodiment of the present invention. A more detailed functional block diagram of the group. Figure 5 is a timing diagram of the operation of the guessing module of Figure 4, in accordance with one embodiment of the present invention.

FIG. 6 is an embodiment of the present invention, which is executed by the ApM control module of FIG. 3 and the PWM controller of FIG. 2 to maximize the map! A flow chart of the control method of the output power provided by the AC adapter. 7A and 7B are timing diagrams of input voltage and input current generated during the control method of Fig. 6. Figure 8 is a more detailed functional circuit diagram of the operation of the adaptive charge controller of Figure 2 in accordance with the present invention. Figure 9 is an illustration of the adaptive charge controller of Figure 2 for use in the MPPT mode for obtaining the maximum power of the solid power sheep from the AC adapter of Figure 1 in accordance with the present invention. Input system e, L John voltage, and wheel power relationship diagram. [Main component symbol description] 10 Charging system 39 201251269 12 Charging control unit 14 Electronic device 16 AC adapter 18 AC power supply 20 System load 22 Charging power supply 24 Input node 26 Output node 28 Adaptive charging controller 29 DC to DC conversion 30 differential amplifier 32 differential amplifier 40 pulse width modulation (PWM) controller 42 constant voltage (CV) control module 44 constant current (CC) control module 46 trickle charge (TR) control module 48 static power Management (SPPM) Control Module 50 Adaptive Power Management (APM) Control Module 52 Maximum Power Point Tracking (MPPT) Module 54 Input Dynamic Power Management (IDPM) Control Module 58 Comparator 60 Adaptive Gain and Filter Circuitry 62 analog to digital converter (ADC) circuit 64 Adaptive gain and filter circuit 40 201251269 66 Digital multiplier circuit 68 Store and compare circuit 70 Digital to analog converter (DAC) circuit 72 Power saving circuit 80 Input - Current - Limit Control Module 82 Common Output Node 84 Common Output Transistor 85 Constant Current Source 86 CLOCK Timing Waveform 87 MEASURE Waveform 8 8 Comparison Node 90 COMPARE Waveform 91 Comparator 92 ADJUST GAIN Waveform 93 Arrow 94 MEASURE&STORE Waveform 96 ADJUST Waveform 9 8 V r Signal 10 0 Flowchart 41

Claims (1)

201251269 VII. Patent application scope: 1. A charger comprising: an input; at least one switch having a first node coupled to a reference voltage; a current sensor coupled to the current Inputting between a second node of the at least one switch; an output coupled to a third node of the at least one switch; and a charge controller coupled to the input and Configuring to determine an input voltage coupled to the current sensor and configured to determine an input current and a plurality of control inputs coupled to the at least one switch, the at least one switch Responsive to controlling the voltage and current at the output of the charger in response to the plurality of control signals supplied by the charge controller to control the voltage and current at the output of the charger, the charge controller being configured to approximately maximize The manner in which the electrical power obtained at the input is input is responsive to the input voltage and the input current to generate the control signals. 2. The charger of claim 1, further comprising a filter coupled between the output and the third point of the at least one switch. 3. The charger of claim 1, wherein the charging control has a plurality of operating modes, @式', which includes a dynamic power management mode, which is required at the input during the dynamic power management mode 式' The electrical power exceeds the electrical power available at the input, and the charging controller is configured by the §2ι in the power management mode of the 201242269 to generate the control signals based on the _reference control signal; The charge controller includes an adaptive power management unit, the T of which is configured to generate the reference control signal, the adaptive power management unit configured to respond in a manner that approximately maximizes the electrical power acquired at the input The input voltage and the input current change the reference control signal. 4. The charger of claim 3, wherein the adaptive power management unit comprises: a first analog-like adaptive gain circuit having a An input for receiving the input voltage and a method for generating an adjusted voltage as the input voltage and a first gain The output of the product; a second analog adaptive gain circuit having a turn-in for receiving the input power and a generating an adjusted current as a product of the input core and a second gain value. An output-converter for converting the adjusted voltage into a discrete voltage value and converting the adjusted current into a discrete current value; a multiplier circuit for generating an input power value as the discrete voltage value and a product of discrete current values; a comparison circuit system for generating a step value proportional to a difference between the input power value and a first-in-coming wheel-in power value; and a second converter for Converting the step value to the reference control signal. . 5. The charger of claim 4, wherein the first type of ratio 43 201251269 should be the same as the discrete voltage value to adjust the first benefit value '俾 to make the discrete voltage The value will be between the previously defined low value ", the number of the charger. For example, the charger of the fourth application of the patent scope, wherein the extreme gain circuit will adjust the number in response to the discrete current value. The :& value '俾 causes the discrete current value to be between a previously defined low value. 7. A battery charger according to item 4 of the Shenqing patent scope, wherein the first-to-first analog gain circuits each comprise an analog signal filtering circuit system. $8. The charger of claim 4, wherein the comparison circuitry includes one or more memory registers for storing the input power value in the one or more memory registers, In order to compare with the input power value determined later, the charger of claim 1 of the patent scope, wherein the charge controller is completely fabricated using an analog circuit system. 10. A charging system, comprising: an adaptor for converting AC electric power into DC electric power, wherein when the DC t flow generated by the adapter is increased above a rated current value, The DC voltage generated by the connector drops rapidly; an electronic device having a power input coupled to at least one rechargeable power source and coupled to at least one circuit for defining a system load; and charging control a unit having an input that is lightly coupled to the adapter, an output that is coupled to the power input of the electronic device, 44 201251269 a sensor for sensing by the transfer The DC current generated by the device and generates a current sensing signal, and switching circuitry that is coupled between the input and output of the charging control unit and responsive to the plurality of control signals generated by the charging control unit so that Supplying the DC voltage and the DC current from the adapter to the charging control unit in a controllable manner, the charging control unit will exceed the DC current required by the electronic device The control signal is generated in response to the DC voltage generated by the adapter when the current is rated and in response to the current signal to approximately maximize the DC power generated by the adapter. 11. The charging system of claim 1, wherein the DC voltage generated by the adapter drops to a predefined value after the DC current required for the charging control unit 7 exceeds the rated current When the voltage value is below, the charging control unit generates the control signals in response to the DC voltage generated by the adapter and in response to the current signal to maximize the DC power generated by the adapter. . /2. The charging system of claim 1, wherein the charging control unit comprises: a charging controller for generating the control signals, the charging controller having a plurality of operating modes, wherein the dynamic power is included The management mode is that during the dynamic power management mode, the DC current required by the charging control unit exceeds the rated current, and the charging controller is operable in the dynamic power management mode for generating based on the reference control signal. The i-control signal; the eight-in-one charging controller includes an adaptive power management unit that generates 4 > test & §fl number' the adaptive power management unit will be maximized by 45 201251269 by the adapter The generated DC electrical power is responsive to the DC voltage generated by the adapter and changes the reference control signal in response to the current signal. 13. The charging system of claim 12, wherein the adaptive power management unit comprises: a first analog adaptive gain circuit having an input for receiving a DC voltage generated by the adapter and An output for generating an adjusted voltage as a product of a DC voltage generated by the adapter and a first gain value; a second analog adaptive gain circuit having an input for receiving the current signal and An output for generating an adjusted current as a product of the current signal and a first gain value; a first converter for converting the adjusted voltage into a discrete voltage value and converting the adjusted current into a discrete current a multiplier circuit 'for generating an input power value as a product of the discrete voltage value and the discrete current value; a comparison circuit system for generating a sum of the input power value and a previously determined input power value The difference between the steps is proportional to the step value; and a second converter for converting the step value into the reference control signal. 14. The charging system of claim 13, wherein the first analog adaptive gain circuit adjusts the first gain value in response to the discrete voltage value such that the discrete voltage value is between a previously defined low Between the value and the high value, 46 201251269 and wherein the second analog adaptive gain circuit adjusts the first gain value in response to the discrete current value, such that the discrete current value is between a previously defined low value and high Between values. 15. A method of supplying DC electrical power from an adapter to an electronic device 'The adapter converts AC current and voltage into DC current and power, wherein the Dc turbulence generated by the adapter When the voltage is raised above a rated current value, the voltage of the Dc generated by the adapter will drop rapidly. The method includes: monitoring one of the DC voltage and the dc current generated by the AC adapter; and if it occurs The monitored DC t voltage drops below a predefined voltage and the monitored DC current exceeds the rated current, then is adapted to approximately maximize the Dc t power supplied by the adapter. The control is supplied to the level of at least one of the % voltage and the DC current of the electronic device by the adapter. < The method of claim 15 wherein the adaptively controlling the level of at least one of the DC voltage and the DC current supplied to the electronic device by the adapter comprises: repeatedly performing the following steps: measuring by The DC current supplied by the adapter generates a corresponding analog current signal; samples the DC voltage and the analog current signal; calculates the supplied power by using the sampled DC voltage as a function of the sampled analog current signal; 47 201251269 Determining a tracking direction toward a larger supply power and a previous supply power value already stored in the memory; adjusting a reference control signal based on the tracking direction; and controlling the rotation based on the reference control signal The connector is supplied to a level of at least one of a DC voltage and a DC current of the electronic device. 1 7 - The method of claim 16, further comprising: amplifying a DC voltage generated by the adapter with a voltage gain value; and amplifying the analog current signal with a current gain value; and wherein Sampling the DC voltage and the analog current signal includes sampling the amplified DC voltage and the amplified analog current signal. 1 8. The method of claim 17, further comprising the step of: prior to adjusting a reference control signal: if the sampled DC voltage is not between a predetermined low value and a high value, The voltage gain value is inversely modified as a function of the sampled DC voltage and the DC voltage amplified by the corrected voltage gain value is sampled until the sampled DC voltage is between the predetermined low and high values. Until the sampled analog current signal is not between the predetermined low value and the high value, the current gain value is repeatedly corrected by the sampled analog current signal as a function and the sampled corrected current gain is sampled. The value-amplified analog current signal 'until the sampled analog current signal is between 48 201251269, which is between the previously determined low and high values; is calculated as a function of the most recently sampled DC voltage and the most recently sampled analog current signal a previously supplied power value; and storing the 5 刖 刖 supply power value in the memory. 19. The method of claim 17, wherein the method further comprises delaying a predetermined period of time between each iteration of the following combination of steps: measuring the DC current, amplifying the dc voltage, and amplifying the analogy The current signal, the amplified DC voltage and the amplified analog current signal, the calculated power, the tracking direction, and the adjustment of the reference control signal. 2. The method of claim 19, further comprising an adaptive power management circuit comprising an electrical circuit for performing the steps of: first S largeizing the DC voltage, amplifying the analog current signal, sampling The DCT voltage and the amplified analog current signal, calculating the supply power m tracking direction, and adjusting the reference control signal; and wherein the method is further included at the previously defined time=will. The adaptive power management circuit is shut down to save the electrical power used by the adaptive power management circuit during the pre-defined chirp period. , Schema: (such as the next page) 49