SE444496B - CLUTCH DEVICE FOR GAS EMISSION POWER DRIVING - Google Patents

Description

10 15 20 25 30 35 8405957-7 2 suitcase device, which with the use of high-frequency plastering nik, provides a distortion-free staining on the net. (See for example, European Patent Application No. 0 013 866). The in-depth comments However, the components are relatively expensive.

According to a third method, the high-frequency plant voltage is used. ning, which is normally attested in the above-mentioned apparatus, that together with a capacitor and a diode provide one poor distortion of the network. Solutions to this principle are described in the two German DE-A1-3222 534 and DE-A1-3319 739. The present invention uses this method, but requires fewer components than the devices according to the aforementioned sealing writings, and gives a hot distortion-free net, in contrast look it the former scripture.

Fig. 1 shows a preferred embodiment of a circuit in a ~ with the invention; Fig. 2 shows the voltage peak in a circuit according to according to the present invention Fig. 1; Fig. 3 shows a circuit according to the present invention for interference compensation; Fig. 4 shows a circuit according to the present invention for symmetry compensation; FIGURE 1. CIRCUIT DESCRIPTION The following description gives the example of Suitable Components values when a standard silent tube (La) of 36 N tax is operated from a network with 220 V, 50 Hz.

Component: C1 10 microF L1 40 mH CZ 25 nF L2, tindn. S1 1 mH C5 500 nF turnover. S1: S2 C6 10 nF 2: 1 C7 5 nF A sinusoidal growth voltage (Um, cza 50 Hz) from a distal ribbon mains are fed into the methane points a and b. 10 15 20 25 30 35 8403957-7 3 one passes a conventional LOW PASS FILTER consisting of The mains voltage is Via the DS Laddas diode Inductive an inductor L1 and a capacitor C5.

Aligned by the rectifier diodes D1-D4. The smoothing capacitor C1 of the rectified current. The voltage L2, together with the diode D0 and SH1, forms a series circuit connectedCharged over C1. PARALLEL with Lindningen 51 on in- ductance L2 Is the capacitor Có. S1 is also loaded throttle charge tube La in series with capacitor C7. From The negative pole on C1 forms a series circuit of the winding S2 and capacitor C2 to the cathode of 05.

SW1 is a suit body, suitably of the semiconductor type, tor, thyristor etLer Similar. SW1 is controlled in a known manner to alternately be Leading, with a frequency of cza 30 Khz. and S2 is such that peak Equal the pipe is lit and the operating conditions Turnover between Lindningen S1 to top the voltage across C1 the value of the AC voltage Ueg is high as (then stabilized). In the example, the turnover is 2: 1.

FIGURE 2 Figure 2 corresponds to the following examples. Here are various voltages and currents plotted Usw1 the basket shape of Along a time axisL. shows the high frequency voltage over SH1. Ueg shows the voltage between points e and g and Young shows the voltage BETWEEN points c and g in Figure 1.

The point g in Figure 1 has the potential NOLL by definition.

Um is the instantaneous mains voltage and Uc1 is the voltage across C1. Ic2 (unfiltered) according to the respective arrows in shows the alternating current through the C2 and Im mains currents, figure 1. a moment when mains voltage- 2b is located Figure 2a shows the time course in an Um is at its peak value. In figure the mains voltage is at its peak value.

FIGURE 1. FUNCTIONAL DESCRIPTION An oscillation circuit is bitten by the inductance L2 and the capacitance C6. A conventional control circuit brings SW1 to Conductor 10 15 20 25 30 35 8403957-7 4 Thereby floating S1, 06, energy tilt position between steps 0 and 1 according to Fig. 2. a current from the capacitor C1 and SN1 to pluspol, genom the negative pole of the capacitor. This is stored in the oscillation circuit L2 / C6. When SW1 breaks this current (in ment 1), an oscillation will start. The oscillation applied res energy from C1, each gang SH1 Leads.

To simplify the explanation, we ignore for the time being the effect that CZ and S2 have on the circuit.

IGNITION OF THE PIPE As we said before, energy is supplied to the oscillation circuit S1 / C6 during each high frequency period. Before the gas discharge tube has ignited only an insignificant part of the brought the energy, so the amplitude of the oscillation is continuous increases. The gas discharge pipe La is parallel via the capacitor C7 Coupled with the oscillation circuit. When the amplitude is over the oscillation circuit has become high enough, the tube lights up. When tube lit consumed As much energy as is supplied, and the amplitude of the oscillation is stabilized.

As can be seen from Fig. 2, the voltage across SN1 is sometimes negative. tiv (moment 3). Diode D6 prevents negative current from flowing. during these moments, which could be the case about SU1 either by SH1 made Leading too early. Some types of switehorgan does not have the ability to block in the reverse direction. A ne- negative current through SH1 would limit the amplitude of the further mentioned the oscillation, the white would make the ignition more difficult of the pipe. However, diode D6 is not ~ necessary for switching the function of the device, and can thus be omitted (short-term tas).

LOAD OF THE NET.

The high frequency AC voltage Ueg has a frequency that is about 600 times higher than the mains frequency. During a period of the high-frequency alternating voltage, the power supply the tension to change significantly, but can be considered as a stable DC voltage. This approach simplifies the 10 15 20 25 30 35 .high-frequency alternating voltage. 8403957-7 S the state of the function of the invention. We assume for simplicity (WF), so that substantially constant over an SO hz period. also because the capacitor C1 is very large its voltage is in EXAMPLE A We are now going to a period of it to study what happens during In the first study, we assume The mains voltage Um is just at its positive peak value de (see Figure 2a). Since the filter L1 / CS is a low-pass filter ter, the voltage across C5 essentially follows the low frequency the voltage Um.

We begin the study in step 2 according to Fig. Za, then the voltage Ueg has its positive peak value. Up to this point, have diode DS has been Leading. The CZ end of the capacitor marked c (C2c), thus has in this moment a potential As high as the positive pole of capacitor C1. In that the voltage Ueg begins to fall, the potential of the capacitor decreases C2 end marked e (C2e). P.g.a. the CZ effect of the capacitor wants thus also the potential of C2c falls. D5 becomes prestressed ' reverse direction and thus blocks. Mains voltage Um over the bridge D1-D4 is, until step 2a, lower than Ucg, why the bridge's diodes also block. The end C2c is thus for the trap is electrically disengaged, and falls at the same rate as end C2e falls.

In step 2a, however, the voltage Ueg has dropped so far, that it becomes as high as the instantaneous mains voltage Um.

In this case, the diodes D1 and 04 in the bridge are biased in the forward direction mains voltage), and continue to be charged from the network, until While C2 is charging, thus a positive current flows 1: 2 through (we study a positive half period at C2 comes in its Ueg reaches its minimum value, in step 3. steps 2a to 3, which is also apparent from the curves kept on and D4 the capacitor C2 from the mains, Ic2 and Im in Fig. 2. The potential in point c the same level as the mains voltage because the diodes D1 leader. This is also shown by the curve Ucg. 10 15 20 25 30 35 8403957-7 6 In step 3, the voltage Ueg begins to rise, due to the LC the oscillation between S1 and C6. Since the end e of C2 (C2e) will also rise the end C2c rise. Thereby blocking D1 and D4 in the pier. DS is also biased in the reverse direction, and blocks why the voltage Ucg will rise in the same way as Ueg. Ucg and Ueg will thus be uniform look moment ia, then Ucg btir As high as Uci. (The thank you The part of the curve Ueg, moment O-1, comes from the fact that SW1 is then dande). to Thereby bLir sä step 3 through step 0 and up to step 2 thus follows CZ, and DS DS biased in the forward direction and will Lead, Long Ueg rises, forward to moment 2. From mo- a current Ic2 to flow from the point g, through S2, to the positive end of Ci. This current Charges seat- des upp C1.

During the studied high-frequency period, all C2 Chargers data from the network (steps 2a-3), and then discharged C1 (torque ia-2). This means that energy has been transferred from the mains TO the capacitor Ci.

EXAMPLE B.

In this example, we study a high-frequency period, during The mains voltage Um is at its peak value (see Fig. Zb). The curves Uswi and Ueg are identical to theirs equivalents in the first example, Fig. 2a.

The course of events is in principle the same as in the previous one example. However, moment Za now occurs later in high frequency. friendship period. The voltage Um is * in this case Lower, and Low and charging only then the voltage Ucg faLLit all the way down to this diodes D1 and D4 will open, C2 may aLLtsä receive one level, of C2 to begin with. Lower Conduction quantity in this period, which is also shown by the curve Ic2. this has it will also take longer Because the voltage Ucg in exempeL a Lower entry level in step 3, in- The negative Become moment 1a. also nan Ucg reaches up to the voltage Uc1 i va The charge pulse through C2 will thus be 10 15 20 25 30 35 8403957-7 7 as shown in curve Ic2. less, NEGATIVE NETWORK PERIODS.

In the above example, we have assumed that the mains voltage negative though has been in a positive half-period. During becomes instead diodes D2 and D3 will half-periods the course of events the same, with the difference that in to be open between steps ia and 2, and that the current pulse Im coming to be negative.

ZERO COMPLETION OF THE MAIN VOLTAGE.

We will now study a high frequency period such as occurs during the moment when the instantaneous value of the mains voltage is zero.

In step 2 according to figure 2 (a and b), the voltage is located Ueg on its positive peak value. Ueg falls between step 2 and 3 to its negative peak value. The turnover between the windings S1 and S2 are designed as above so that the the peak voltage of Ueg is equal to the voltage Uc1.

Between steps 2 and 3, the end e of the capacitor thus falls C2 (C2e) Uci volt. It follows that the end CZC also strives \ after falling Uci volts. Because the output potential of Ucg (in step 2) was Uci volt, striving Ucg was sold to fall down to zero.

In the case now being studied, Ucg will fall all the way down to zero (in step 3 according to figure 2). Since mains voltage- one is zero, diodes D1-D4 will never be biased in the direction and open. The capacitor C2 thus enters to receive any charge from the network during this frequency period.

SINUS-SHAPED AC POWER We have seen in the reasoning under the previous heading, that striving to though instead, the capacitor C2 of the the voltage Ucg, in step 3 according to figure 2, reach potential zero. In examples a and b above, we have seen that the mains voltage in de c (C2c) to the mementian voltage. The capacitor 10 15 20 25 30 35 8403957-7 8 Thus, CZ may receive a Charge in each high frequency period from the mains, against the instantaneous mains voltage which is proportioneLL The average value of the current with which C2 tests the network bLir ningen. during a high frequency period, thus proportional to the torque value of the mains voltage.

Disregarding the high frequency pulses in the mains current Im, which the device generates, and only looks at the average that of the mains current, calculated over each high frequency period, one finds that the mains current, hot time is proportioneLL to the instantaneous mains voltage Um. Because the mains voltage_ is sinusoidal The mains current also becomes sinusoidal and in phase with the mains voltage.

The high frequency component, as the mains Im going to be removed in a known manner by the Low Pass Filter achieved the distortion-free mains current contain, filtered L1 / CS. Thus we have but, which is one of the objects of the invention.

OTHER CURVE FORM With the knowledge as above about the function of the coupling device tion, one also realizes that the desired distortion-free the mains current is achieved regardless of the waveform of the voltage Ueg. The only requirements that need to be placed on this voltage are that its peak-to-peak amplitude is As high as the voltage Uc1, Because the voltage CZ, det which DC voltage level (average level) voltage and that its frequency is constant. to role, Ueg is transmitted via a capacitor player either Ucg No ningen Ueg swings.

Capacitor C1 as we have seen current pulses from C2. and Charging current to C1. C1 is discharged by the current Laddas, The larger the capacitor C2, the larger it becomes. OVân, âV the components to the right of C1 in Figure 1 consume. Power supply the consumption increases, the higher the voltage Uc1 is. By increasing OR reduce the capacitance of capacitor C2, it can current carried to C1 is increased and decreased, respectively. Thus can be sated voltage level Uc1 is increased or decreased, and set to 10 15 20 25 30 35 8403957-7 desired value.

If the load is not constant, the inflow can be regulated in different ways, as described below.

In the above job description, we have assumed that the capacitance of C1 is very high. The capacitance values that used in practice (10 microfarads in the above pel), means that the voltage Uc1 will vary slightly, the network frequency. Since also with a frequency corresponding to double that the voltage UC1 decreases, the amplitude of the voltage Ueg to decrease, as this is generated with the help The requirements set above for the voltage Ueg (see in other words by Uc1. heading "Other curve shape"), will still be be met.

COUPLING FOR INTERRUPTION COMPENSATION In coupling devices for driving gas discharge pipes at high frequency radio interference is generated. These are mainly mainly due to capacitive coupling between parts of the rate, as for high frequency voltage, and the housing of the device.

FIGURE 3 Component list: C1 10 microF 'L1 40 md C2 25 nF Ls, lindn. S1 0.25 mH C5 500 nF lindn. S1b 0.25 mH C6 20 nF turnover.S1: S1b: S2 Cov 20 nF ¿1: 1: 1 C? 10 nF C7b 10 nF According to the invention, a very large proportion of these voltages are eliminated with a coupling according to figure 3. Here two parts, compared to copper C6 has been divided into The switching device SW1 has been moved and connected and S1b. the winding S1 has been divided into according to Figure 1. Also the capacitor two, C6 and Cób. in the middle between the two sub-windings S1 10 15 20 25 30 35 8403957-7 10 the charging tube La has here, via C7 and C7b, been connected in parallel with the switching means SW1.

The coupling according to figure 3 works in principle in the same way as the device according to figure 1. Also the curves according to figure 2 are applicable to Figure 3.

In terms of AC voltage, the gas discharge pipe is still running in parallel with the LC circuit S1 + S1b / C6 + C6b, ef- since C1, in terms of AC voltage, connects the upper end the one on S1 with the lower end of S1b.

Points h and j according to Figure 3, will lead to high frequency expect AC voltages that could cause radio interference. Exciting however, the respective points are uniform According to nings in men the coupling device is built that the two points have the same capacitance opposite. the invention mechanically up so, to to take each other out, In this case, the two interfering voltages so that the housing of the device. radio interference practically taken is eliminated. Also the voltages that occur at the gas discharge pipe Both ends can normally cause radio interference. In the clutch according to figure 3, these two disturbing voltages will also take out each other.

The low level of radio interference usually means something extra does not need to be used. cup- as effective radio interference filter This does cheap and reliable, at the same time the degree of increase is increased. 3 connected to the upper S1b The end e, of the capacitor C2 is i S2. figure The turnover between 1: 1. the same end of the winding (half S1) the winding and S2 is that C2: s normally This means tension the point in point h, is as in point e. end e can thus be connected to the point h, and the winding S2 pas. This, of course, cheapens the device. 10 15 20 25 30 35 8403957-7 11 under the heading "Other curve shape" equal According to what is explained above, the end e of the capacitor C2 can be connected point j in Figure 3.

Then the winding S2 is eliminated as above, and C2e is connected h, does not apply Longer complete symmetry between voltage respectively h. occurs and S1b has arna i punktna j Osymmetrin p g a that the windings S1 different load, and by the magnetic coupling between them in practice never can become ideal.

FIGURE 1. ° Component list: C1 10 microF L1 49 mH CZ 12.5 nF L2, lindn. S1 0.25 mH C2b 12.5 nF lindn. Sib 0.25 mH C5 S00 nF turnover. S1: S1b C6 20 nF 1: 1 Cov 20 nF C7 10 nF C7b 10 nF With a coupling device according to Figure 4, however, this is Here, the capacitor C2 has also been divided into two C2 and C2b. the diode DS has also been replaced by two diodes, problem solved. equal capacitors To obtain full symmetry, have DS and D5b.

The complexes S1, C2 and DS work in this coupling device in the same way as the corresponding components in the previous Sïb, C2b and D5b work but with reverse polarity on the voltage and written connections. The complex in an analogous manner, streams.

REGULATION According to the invention, the power taken out of the mains regulated in several ways.

Varying frequency The power taken out of the mains is proportional to it 10 15 20 25 30 35 8403957-7 12 the frequency of the high-frequency alternating voltage. By varying frequency according to known methods (see, for example, European application number 0 065 794), can thus the drawn network power varies.

Varying capacitance The mains power taken is also proportional to the condensate C2 with capacitors If- tower C2 capacitance. By replacing of different capacitance, the mains power can thus be varied. the connection between different capacitors can be made using mechanical switches, relays or switching means of semiconductor devices type.

Switch control According to the invention, the diode DS can be replaced by a thyristor, or connected in series with another suitable switching means (e.g. transistor). By controlling this switch means to be open only during some of the high frequency periods, one can regulate the output power. The two diodes DS and D5b according to Figure 4 can also be replaced. taken and controlled according to the above principles.

According to the invention, several gas discharge pipes (La) can be used associated capacitor (s) (C7 / C7 + C7b) parallel connected to each other, according to the dashed part of the figure 1, 3 or 4. The method is not limited to two pipes, but can be used for an unlimited number of pipes.

According to the invention, the gas discharge tube (s) can be connected in over one or more additional wires on the inductance L2.

This can be suitable if you want to use pipes with a pile ignition voltage. The extra windings can also be connected in series with the ordinary windings.

COMPARISON WITH KNOWN CONSTRUCTIONS Below, comparisons are made with the technology known today, in order to demonstrate the advantages of the present invention. 10 15 20 25 30 35 8403957-7 13 European Patent Application 0 D13 866 The coupling device according to EP 0 D13 866 requires 5 switch ~ (S1, S2, S3, S4, S7), performance as present components to achieve the same technical invention provides with only a suit component of comparable type. Compared with the present the invention, the above device is thus significant more expensive, and have poorer reliability.

German Offenlegungsschrift DE 33 19 739 assume: The 33 19 739 requires 2 swätchkompoenref <9.1o according to The advantageous disturbed ~ figure 1), against one of comparable type. pension achieved according to the present invention can not obtained according to DE 33 19 739.

German Explanatory Memorandum DE 32 22 534 According to DE 32 22 S34, 2 switch components (T1, T2) are also required against one of comparable type. The advantageous the interference compensation obtained according to the present invention not obtained according to DE 32 22 534. according to figure 1) can

Claims (6)

10 15 20 25 30 35 8403957-7 14 PATENT CLAIMS Coupling device for driving gas discharge pipes with from an alternating (cza 50 current becomes (cza 30 Khz) alternating voltage (Uswi) (Um) with significantly low-frequency high-frequency voltage source lower. Frequency hz), where essentially distortion-free, CS), a bridge rectifier (D1-D4), the alternating voltage source consisting of a low-pass filter (L1, a smoothing capacitor (C1), a switching means (SH1), and an oscillating circuit (L2, Có), and where the low-frequency alternating voltage (Um) is filtered by the low-pass filter (L1, CS) and is rectified by the rectifier bridge (D1-D4), where a circuit is formed by at least the smoothing capacitor (C1), the inductance in the oscillating circuit (L2) and the switch means (SW1), and where high frequency alternating voltage (Usui, Ueg) is generated by periodically closing and opening the switching means (SW1), whereby energy is transferred from the smoothing capacitor (C1) to the oscillating circuit (L2, Có), and where a gas discharge tube (La) is intended to be connected to one of the high-frequency alternating voltage source outputs (Usw1) via at least one capacitor (C7), characterized in that the filtered and rectified voltage, via a connection in which at least one diode (DS) is included, is arranged to be supplied to the smoothing capacitor (C1), that a capacitor (C2) is connected at one end (C2c) to the connection between the rectifier bridge (D1-D4) and the diode (DS), and at its other end (C2e) is connected to an output (e) of the high-frequency alternating voltage source, wherein the capacitor (C2) Charged from the low-frequency alternating voltage source (Um), via at least the low-pass filter (L1, CS), the rectifier bridge (D1-D4) and an output from the high-frequency alternating voltage source (e) under part of the high-frequency of the AC voltage (Ueg> period (steps 2-3) and where the capacitor (C2) is charged in the opposite direction, via at least 10 15 20 25 30 35 8403957-7 15 from the high frequency and smoothing capacitor the AC voltage source (e), (C1), (Ueg ) an output (DS) the high frequency diode during another part of growth The voltage period (steps 3-2). characterized by interpolating the partial winding Coupling device according to claim 1, (L2) of each ductance i has sub-windings (S1, Sib), (j, h) will generate a high frequency alternating voltage each, the oscillation circuit where one end resp. where these two alternating voltages are substantially uniform but opposite, with capacitively coupled interfering currents, from these two (j and h) and other high-frequency alternating voltage sources within the coupling device, to the coupling device housing, substantially canceling each other out. Coupling device according to claim 2, characterized in that in filtered and rectified (01), that a further capacitor the connection which supplies it to (OSb>, connected to additional (C2b) is the rectifier voltage - the smoothing capacitor is included in more than one diode connection between (D5b) an output (h) of the high-frequency alternating voltage, the capacitor (C2b) being charged from the low- (Um), via at least low-pass- at one end of the bridge (D1-D4) and the diode and at its other end is connected to the voltage source, the frequent alternating voltage source from the high-frequency alternating voltage (Ueg) 2-3) (C2b) is charged via output from the high-frequency (D5b) filter and an output period (torque and where the capacitor in the opposite direction at least one alternating voltage source) , the diode and the smoothing capacitor (C1), during another part of the high-frequency alternating voltage (Ueg) period (steps 3-2). Coupling device according to claim 2 or 3, wherein the high-frequency alternating voltage source has two outputs (j, h), the voltages of which are in opposite phase, characterized in that the gas discharge tube (La) is intended to be connected to said outputs (C7, C7b ) of equal capacitance, where a capacitor (C7, C7b) is intended via at least two capacitors with substantially 10 to be bounced at each end of the gas discharge tube, capacitively coupled interference currents, from both gas discharge tube ends, to the housing of the coupling device, essentially cancel each other out. S. Coupling device according to claim 1,2 after 3, characterized in that the gas discharge tube (La) and the capacitor in series with the tube (C7} are connected in parallel with another or four tubes, each in series with another capacitor. Coupling device according to claim 4, characterized in that the gas discharge pipe (La) and the capacitors (C7, C7b) in series with the pipe are connected in parallel with another after another pipe, each in series with two more capacitors each.