RU2714672C1 - Device for determination of target movement parameters - Google Patents

Abstract

FIELD: radar ranging and radio navigation.

SUBSTANCE: invention relates to radar ranging, in particular, to devices for determining target motion parameters in bistatic radar systems. Technical result is achieved due to that device comprises transmitting position consisting of transmitter, transmitting antenna, and located away from radiation source receiving position consisting of receiving antenna, first and second adders, which outputs are connected to first and second receivers inputs, angular discriminator, trajectory parameters calculation unit, also comprises a second receiving antenna, series-connected first phase shifter block, third adder, third receiver, matched filter, first detector and calculating unit ΔR, second and third phase changer units, first and second controlled matched filters, series-connected fourth adder, fourth receiver, matched filters unit and maximum selection unit, first and second switches, second detector, third, fourth keys and control voltage generation unit.

EFFECT: high accuracy of measuring location of a target in the entire region of possible signal reception, shorter time for measuring coordinates, as well as high noise-immunity of operation of the luminous bistatic radar station.

4 cl, 12 dwg

Description

The invention relates to the field of radar, in particular to devices for determining the parameters of the movement of the target in bistatic radar systems.

It is known "Device for determining the parameters of the movement of the target" (RF Patent No. 2168740, IPC G01S 13/06, published on 06/10/2001 Bull. No. 16), containing a transmitting position and located at a remote point receiving position, consisting of an antenna , a receiving device, a unit for measuring the Doppler frequency, a unit for measuring the direction of arrival of the interference signal, a unit for extrapolating the measured parameters, a unit for calculating the instant of time when the target intersects the base line, a unit for determining the position surface, a unit for calculating the path parameters, b lock division of the reference voltage of the summing device, the unit for identifying signals by frequency and subtracting false signals.

A probing continuous (unmodulated) signal emitted by the transmitting position having a wide antenna pattern (BOTTOM) in the azimuthal plane is received at the remote point by the antenna system of the receiving position formed by the partial channels. The received direct transmitter signal and the signal reflected from the target at the output of the parallel channels form low-frequency oscillations of the interference beats that enter the Doppler frequency measuring unit. In the unit for measuring the direction of arrival of the interference signal, the angular coordinate of the target is determined.

On the basis of measurements of the Doppler frequency and angular coordinates, the extrapolated time instant of the target crossing the base line to the span of the target line is determined. The position surfaces are determined and, taking into account measurements of the angular coordinates, the trajectory parameters of the target are determined. The spatial coordinates of the target are uniquely determined as the coordinates of the point of intersection of the position surface and the direction line to the target from the receiving position (bearing line).

The disadvantage of this device is the low accuracy of determining the motion parameters of the target, due to the fact that:

- extrapolation of the Doppler frequency and angular coordinate until the target crosses the base line in some cases for a considerable time, for example, when the target is flying at small angles to the base line, which leads to an increase in the measurement errors of the total range, and, consequently, to determination errors slant range;

- accompanied by intensively maneuvering targets, the extrapolation of the Doppler frequency until the target crosses the base line is carried out with significant dynamic errors, since there is no a priori information about the intensity of the maneuver of the target, and after the target crosses the base line, integration for a long time also leads to range determination errors.

It is known "Device for determining the parameters of the target’s movement" (Patent for utility model of the Russian Federation No. 107370, IPC G01S 13/06, published on 08/10/2011, Bull. No. 22) containing a transmitting position consisting of a transmitter and a transmitting antenna, and A receiving position located at a point remote from it, consisting of a receiving antenna, two circuits, including a receiver, detector and low-pass filter connected in series; a trajectory parameter calculation unit; a first Doppler frequency measurement unit, a transmitting position, contains serially connected the second transmitter and the summing unit, the receiving position further comprises a separation unit, a third circuit consisting of a series-connected receiver, detector and low-pass filter, a separation unit, a phase difference meter, an aggregate range estimation unit, a second Doppler frequency measurement unit, a rate of change rate estimation unit the directions of arrival of the interference signal, and the scaling unit

The transmitting position generates two monochromatic probing signals. The receiving position receives signals propagating along the base line and signals that have passed along the path of the transmitting position - target - receiving position. The phase method determines the total range, and based on the analysis of Doppler frequencies, the rate of change of the total range. An estimate of the direction of arrival of the interference signal is determined by the phase method, and the angular velocity of the direction of arrival of the interference signal is determined by the measured value of the Doppler frequency and the angular coordinate. In the block for calculating the trajectory parameters, the distance to the target relative to the receiving position is determined, with the known value of the base, the total range and the angular coordinate. Next, rectangular coordinates and their change rates (projections of the target velocity vector on the axis of a rectangular coordinate system) are determined.

The disadvantage of this device is the assumption of the same value of the phase jump at both frequencies when the signal is rereflected from the target. Failure to comply with this assumption leads to errors in the determination of coordinates. In addition, when the signal propagates along the base line, as well as along the line, the transmitting position - the target receiving position may reflect signal reflections from the earth's surface, which also affects the accuracy of measuring phase differences, and therefore the total range. The use of monochromatic signals leads to low stealth and noise immunity of the system.

Known "Device for determining the parameters of the target movement" (Patent for utility model of the Russian Federation No. 109869, IPC G01S 3/46, publ. 10/27/2011 Bull. No. 30), containing the transmitting position, consisting of series-connected transmitter and antenna, and at a point remote from it, the receiving position, which consists of an antenna of the receiving position, having N outputs, each of which, except for the central one, is connected to one of the inputs of the corresponding summing device, the output of which is connected to the corresponding receiver, and the central output of the antenna is connected to ohms of dividing the reference voltage, the receiver of the central partial channel, the summing devices of the corresponding partial channels, the azimuth determination unit of the antenna pattern of the transmitting position of the trajectory parameter calculation unit, while the transmitting position transmitter comprises serially connected synchronization unit, frequency synthesizer, power amplifier and beam control unit and a block for calculating the path parameters, the output of which is the output of the entire device.

The antenna of the transmitting position, scanning the space in a given sector, emits a continuous (modulated) signal at various frequencies in certain directions of the space sector. In the process of reviewing the space when moving the bottom of the transmitting position by a certain angle, the frequency of the probing signal generated by the transmitting position changes. Thus, the current value of the carrier frequency of the probing signal is related to the angular direction of sensing of the transmitting position. The direct signal formed by the side lobes of the bottom of the transmitting position is received by the central (main) bottom of the receiving spatial channels of the receiving position. It is used as a reference signal, analyzing the value of the frequency, which can determine the direction of radiation at the transmitting position. The unit for measuring the direction of arrival of the interference signal measures the azimuth of the target relative to the receiving position. In the block for calculating the path parameters, the distance to the target is calculated based on the results of solving the triangulation problem with respect to the receiving position, the rectangular coordinates of the target are determined.

The disadvantage of this device is the low secrecy and noise immunity of the device, due to the use of monochromatic signals, since setting interference from a space zone at a different frequency can lead to a false measurement of the bearing relative to the transmitting position. In a number of areas of space, the accuracy of determining the location may decrease, which is caused by the specificity of the geometric factor of accuracy inherent in the triangulation method of determining coordinates. In addition, with a significant number of targets in the field of view, the problem of intersecting false points of intersection of bearings may arise.

Closest to the technical nature of the claimed device is a "Device for determining the parameters of the target movement" (RF Patent No. 2584332, IPC G01S 3/00, publ. 05/20/2016, Bull. No. 14), containing the transmitting position, consisting of sequentially connected transmitter and antenna, and at a point remote from it, the receiving position, which consists of the antenna of the receiving position, having N outputs, where N is the number of partial receiving spatial channels mutually overlapping at half power level, each of the outputs, except for the central one, is connected with one of the inputs of the corresponding summing device, the output of which is connected to the input of the corresponding receiver, and the central output of the antenna is connected to the input of the reference voltage division unit with N outputs, the corresponding output of which is connected directly to the input of the receiver of the central partial channel, and the remaining N-1 outputs connected to the second inputs of the summing devices of the respective partial channels, the block determining the azimuthal position of the radiation pattern of the antenna transmitting pos the input, which is connected to the second output of the receiver of the central partial channel, and the output is connected to the second input of the trajectory parameter calculation unit, while the transmitter of the transmitting position contains serially connected synchronization unit, frequency synthesizer, power amplifier and beam control unit, the second input of which is connected to the second output of the synchronization unit, and the output is connected to the input of the transmitting antenna, while the outputs of the receiver of each of the partial channels are separately connected to the corresponding and the inputs of the unit for measuring the direction of arrival of the interference signal, the output of which is connected to the first input of the unit for calculating the trajectory parameters, while the Doppler frequency measuring unit, the extrapolation of the measured parameters (dependences of the Doppler frequency and the angular direction to the target in time), the moment calculation unit are introduced the target crossing the base line and the position surface determining unit, the output of which is connected to the third input of the trajectory parameter calculation unit, and a unit for calculating the target’s flight altitude, the corresponding input of the unit for measuring the Doppler frequency being connected to the output of the corresponding receiver, the second input of the unit for extrapolating the measured parameters is connected to the output of the unit for measuring the direction of arrival of the interference signal and to the first input of the unit for calculating the altitude of the target’s flight, also associated with the first output of the unit computing trajectory parameters, the second input of the position surface determining unit is connected to the output of the extrapolation unit of the measured parameters, the second input the target altitude calculation unit is connected to the output of the azimuthal position determination unit of the antenna pattern of the transmitting position, the third input of the target altitude calculation unit is connected to the output of the trajectory parameter calculation unit, and the output of the target altitude calculation unit is the output of the entire device.

The antenna of the transmitting position, scanning in a given sector, emits a continuous signal at various frequencies, with each angular direction of sounding corresponding to a certain carrier frequency. The receiving position based on the analysis of the received oscillations determines the angle at which the target is irradiated. In the unit for measuring the direction of arrival of the interference signal, the target azimuth value is generated relative to the receiving position, and in the block for calculating the path parameters, the distance to the target is calculated based on the results of solving the triangulation problem relative to the receiving position and the rectangular coordinates are estimated.

Based on measurements of the direction of arrival of the interference signal and the Doppler frequency, in the extrapolation unit of the measured parameters, the functional dependences of the Doppler frequency and the direction of arrival of the interference signal on time are extrapolated. In the extrapolation unit of the measured parameters, the measured values of the Doppler frequency and the angle of arrival of the interference signal are extrapolated at the moment the target crosses the base line. In the unit for calculating the instant of time when the target crosses the base line, the extrapolated time instant when the target crosses the base line until the target passes this line is approximately determined. Next, the device calculates the total range and altitude of the target.

The disadvantages of the known prototype device are: low accuracy of measuring the location of the target in the entire area of the space of the possible reception of signals, the time delay in obtaining an estimate of the coordinates of the target, as well as low noise immunity.

These shortcomings are due to:

1. Obtaining an estimate of the azimuthal position of the target relative to the transmitting position by the number of the angular position of the antenna pattern of the transmitting position, determined by the value of the frequency of the monochromatic signal emitted in this position. As a result, the measurement accuracy is determined by the width of this radiation pattern.

2. The need to perform extrapolation of the trajectory of the target with possible errors that occur during its maneuvering, which also leads to a delay in determining the coordinates.

3. A significant dependence of the accuracy of measuring the location of the target on its position relative to the base line, when approaching this line, measurement becomes impossible.

4. The use of a monochromatic emitted signal in the prototype, which determines the low stealth of the work, and, therefore, the low noise immunity of its work in relation to the interference aiming in frequency, which together leads to low noise immunity.

The main objective of the claimed invention is the creation of a device that allows you to measure the location of the target in the field of possible signal reception with greater accuracy.

The technical result is to increase the accuracy of determining the location of the target in the entire area of the possible reception of signals and increase the noise immunity of the luminal radar.

The specified technical result is achieved by the fact that in a device containing a transmitting position consisting of a transmitter, the output of which is connected to the input of the transmitting antenna and located at a distance from the radiation source, the receiving position consisting of a receiving antenna, first and second adders, the outputs of which are connected respectively to the inputs the first and second receivers, as well as the angular discriminator and the block for calculating the trajectory parameters, an additional second receiving antenna is introduced, connected in series with the first phase shifter lock, third adder, third receiver, matched filter, first detector and ΔR calculation unit, the output of which is connected to the second input of the trajectory parameter calculation unit, the third input of which is the input of the range value L, the inputs of the first phase shifter block are connected to the outputs of the receiving antenna, the second and third blocks of phase shifters, the inputs of which are connected to the outputs of the second receiving antenna, and the outputs are connected to the inputs of the first and second adders, the first and second controlled matched filters, the outputs of which are connected respectively with the outputs of the first and second receivers, and the outputs are with the inputs of an angular discriminator, a fourth adder, a fourth receiver, a matched filter unit and a maximum selection unit, the first and second outputs of which are connected to the first inputs of the first and second keys, respectively , the third output is connected to the input of the second detector, the output of which is connected to the second inputs of the first, second, third, fourth keys and the second input of the calculation unit ΔR, and, ne the second and second inputs of the fourth adder are connected to the outputs of the first and second adders, respectively, the control voltage generation unit, the first output of which is connected to the second inputs of the first and second controlled matched filters, the second output is connected to the third inputs of the first and second controlled matched filters, the outputs of the first and the second keys are connected to the first and second inputs of the block generating control voltages, respectively, and the fourth and fifth inputs of the block for calculating the path parameters, in the output of the angular discriminator is connected to the input of the third key, the output of which is connected to the first input of the trajectory parameter calculation unit, the output of which is connected to the first input of the fourth key, the output of which is the output of the entire device, the second output of the transmitter is connected to the second input of the transmitting antenna.

The transmitter contains a frequency synthesizer, a first power amplifier, the output of which is the first output of the transmitter and connected to the first input of the transmitting antenna, additionally introduced the first and second phase shifters, the inputs of which are connected to the output of the frequency synthesizer, and the outputs, respectively, to the first inputs of the first and second key stages, the second inputs of which are connected to the output of the pseudo-random sequence generator, the output of the first key stage is connected to the input of the first power amplifier, and the output of the second key Vågå stage via a second power amplifier whose output is the second output of the transmitter is connected to the second input of the transmitting antenna.

The first controlled matched filter contains a delay line with taps, the input of which is the first input of the first controlled matched filter, and its outputs are connected to the inputs of the block of controlled phase shifters of the frequency tuning corresponding to them by number, the control input of which is the third input of the first controlled matched filter, part of the block outputs controlled phase shifters of the frequency tuning are connected to the inputs of the first adder, the first controlled matched filter, the output of which through the first controlled phase shifter of the azimuthal tuning of the first controlled matched filter is connected to the first input of the third adder of the first controlled matched filter, the other part of the outputs of the block of controlled phase shifters of the frequency tuning is connected to the inputs of the second adder of the first controlled matched filter, whose output connected to the second input of the third adder of the first managed matched filter through tionary phase shifter connected to «π» and second controllable phase shifter azimuthal settings managed first matched filter, whose output is the output of the first matched filter managed, the control inputs of the first and second phase shifters controlled azimuthal settings managed first matched filter connected to its second input;

The matched filter block contains a delay line with taps, the input of which is the input of the matched filter block, and the outputs are connected to the N inputs of the N phase frequency shifter blocks matching them by number, some of the outputs of which are connected to the N inputs of the first adders corresponding to them by the number whose outputs are connected to the corresponding to them number N of the first blocks of phase shifters of tuning in M directions, the other part of the outputs of each of the N blocks of phase shifters of frequency tuning is connected to the corresponding the number of inputs of the second adders, the output of each of which through the corresponding phase shifter to "π" is connected to the corresponding inputs of the second blocks of phase shifters of tuning in M directions, the M outputs of each of the first blocks of phase shifters of tuning in M directions are connected to the corresponding first inputs by number M two-input adders, the second inputs of each of which are connected to the outputs of the second blocks of phase shifters of tuning in M directions corresponding to them by number, the outputs of each of which are are connected to the inputs of M amplitude detectors, the outputs of which are the outputs of the entire block of matched filters.

The technical result is achieved through the introduction of new blocks and relations between them, which allow:

- to separate the signals passing the path from the transmitting to the receiving position directly - (direct signal) and reflected from the target, passing the path - transmitting position - target - receiving position, using the introduced second receiving antenna, the second block of phase shifters and the third block of phase shifters included at its output also connected in series - the first block of phase shifters, the third adder, the third receiver, the matched filter, the first detector and the unit for calculating ΔR of the distance difference;

- use for measuring the azimuthal direction of the target relative to the transmitting position a complex spatio-temporal (PV) phase-shift (FM) emitted signal obtained by introducing into the transmitter the transmitting position, new units such as the PSP generator, the first phase shifter, the second phase shifter, the first key cascade, the second key cascade, the second power amplifier and the connections between them, which made it possible to measure the location of the target in the field of possible signal reception with greater accuracy and increase the noise immunity of the luminal radar;

- get a more accurate estimate of the angular coordinate of the target relative to the transmitting position using the newly introduced sequentially connected fourth adder, fourth receiver, matched filter block, maximum selection block, second detector;

- to get a more accurate estimate of the target angle relative to the receiving position using the newly entered first key, second key and control voltage generating unit, first controlled matched filter, second controlled matched filter, as well as first key, second key and control voltage generating block;

- receive, due to the newly introduced blocks and the links between them, estimates of the target’s location without applying the extrapolation mode of the target’s trajectory over almost one period of the pseudo-random sequence (PSS) emitted by the transmitting position or one pulse of a complex FM signal with pulsed radiation, and also allows you to accurately determine the difference between the distances ΔR transmitted by the direct and re-emitted target signals, for one period of the SRP or one pulse of a complex FM signal, which increases the area of accurate measurement of coordinates goals. This is especially important when approaching the target trajectory to the line connecting the transmitting and receiving positions.

The invention is illustrated by drawings, where in FIG. 1 shows a structural diagram of the inventive device and the following notation:

1 - transmitter;

2 - transmitting antenna;

3 - receiving antenna;

4- first adder;

5 - second adder;

6 - the first receiver;

7- second receiver;

8 - angular discriminator;

9 - block computing trajectory parameters;

10 - the second receiving antenna;

11 - the first block of phase shifters;

12 - the third adder;

13 - the third receiver;

14 - matched filter;

15 - the second block of phase shifters;

18 - the third block of phase shifters;

19 is a first controlled matched filter;

20 is a second controlled matched filter;

21 - the fourth adder;

22 - the fourth receiver;

23 - block matched filters;

24 - block selection of the maximum;

25 is the first key;

26 - the second key;

27 - the second detector;

28 - the third key;

29 - the fourth key;

30 - block generating control voltages;

figure 2 shows the structural diagram of the transmitter and the following notation:

1 - transmitter;

1.1 - frequency synthesizer;

1.2- generator PSP;

1.3 - the first phase shifter;

1.4 - the second phase shifter;

1.5 - the first key cascade;

1.6 - the second key cascade;

1.7 - the first power amplifier;

1.8 - second power amplifier;

2 - transmitting antenna;

in FIG. 3 - shows the formation of the emitted P-V signal on the example of a seven-element Barker code;

in FIG. 4 presents an implementation option block matched filters (SF) and introduced the following notation:

23 - block matched filters;

23.1 - delay line with bends;

23.2i - the i-th block of the PV of the frequency tuning, i = 1 ÷ N;

23.3i - the i-th first adder of the PV unit of the frequency tuning, i = 1 ÷ N;

23.4i - the i-th second adder of the PV unit frequency tuning, i = 1 ÷ N;

23.5i-i-th PV on "π", i = 1 ÷ N;

23.6i - the i-th first block of the PV settings for M directions, i = 1 ÷ N;

23.7i - the i-th second block of the PV settings for M directions, i = 1 ÷ N;

23.8. (I.j) - (i.j) -th two-input adder, i = 1 ÷ N, j = 1 ÷ M;

23.9. (I.j) - (i.j) -th amplitude detector, i = 1 ÷ N, j = 1 ÷ M;

in FIG. 5 shows a variant of the analog implementation of one i-th frequency channel with tuning in M directions of the possible signal arrival from the target of the SF block 23 for the 7-element Barker code,

in FIG. 6a, 6b depict a variant of the analog implementation of controlled matched filters (SF) 19 and 20 and the notation is introduced:

19 is a first controlled matched filter;

19.1 - delay line;

19.2 - block controlled phase shifters (PV) frequency tuning;

19.3 - the first adder of the first managed matched filter;

19.4 - the second adder of the first managed matched filter;

19.5 - PV on "π";

19.6 - the first controlled PV azimuthal settings;

19.7 - the second controlled PV azimuthal settings;

19.8 - the third adder of the first managed matched filter;

20 is a second controlled matched filter;

20.1 - delay line;

20.2 - block controlled PV frequency tuning;

20.3 - the first adder of the second managed matched filter;

20.4 - the second adder of the second managed matched filter;

20.5 - PV on "π";

20.6 - the first controlled PV azimuthal settings;

20.7 - the second controlled PV azimuthal settings;

20.8 - the third adder of the second managed matched filter;

in FIG. 7 shows an embodiment of one of the managed SFs for the 7-element Barker code,

in FIG. 8 shows the geometric relationships for determining the location of the target for a two-position luminal radar,

in FIG. Figure 9 shows the RMS values for determining the target’s flight altitude at a base value of L = 50 km, the target performs a straight flight at an altitude of 5000 m perpendicular to the base line at a speed of 200 m / s with initial coordinates X = 20 km, Y = 15 km.

in FIG. 10 shows the RMS values for determining the target’s flight altitude under the same conditions (Fig. 9), but the target flies at an angle to the base line of 60 deg.

in FIG. Figure 11 shows the standard deviation for determining the coordinates when flying the target parallel to the X axis (base line) at Ho = 45000 m, Yo = 5000 m

Fig. 12 shows the standard deviation for determining the coordinates when flying the target parallel to the X axis (base line) at Xo = 45000 m, Yo = 500 m.

The device for determining the parameters of the target’s movement contains a transmitting position consisting of a transmitter 1, the output of which is connected to the input of the transmitting antenna 2 and located at a distance from the radiation source receiving position consisting of a receiving antenna 3, the first 4 and second 5 adders, the outputs of which are connected respectively to the inputs of the first 6 and second 7 receivers, as well as the angular discriminator 8 and the block for calculating the path parameters 9, the second receiving antenna 10, connected in series to the first block of phase shifters 11, third the adder 12, the third receiver 13, the matched filter 14, the first detector 15 and the calculation unit ΔR 16, the output of which is connected to the second input of the trajectory parameter calculation unit 9, the third input of which is the input of the range value L, the inputs of the first block of phase shifters 11 are connected to the outputs receiving antenna 3, second 17 and third 18 blocks of phase shifters, the inputs of which are connected to the outputs of the second receiving antenna 10, and the outputs to the inputs of the first 4 and second 5 adders, the first 19 and second 20 controlled matched filters, the first the inputs of which are connected respectively with the outputs of the first 6 and second 7 receivers, and the outputs with the inputs of the angular discriminator 8 are connected in series to the fourth adder 21, fourth receiver 22, matched filter block 23 and the maximum selection unit 24, the first and second outputs of which are connected to the first inputs of the first 25 and second 26 keys, the third output is connected to the input of the second detector 27, the output of which is connected to the second inputs of the first 25, second 26, third 28, fourth 29 keys and the second input of the calculation unit ΔR 16, and, p the first and second inputs of the fourth adder 21 are connected to the outputs of the first 4 and second 5 adders, respectively, the control voltage generation unit 30, the first output of which is connected to the second inputs of the first 19 and second 20 controlled matched filters, the second output is connected to the third inputs of the first 19 and second 20 controlled matched filters, the outputs of the first 25 and second 26 keys are connected to the first and second inputs of the control voltage generation unit 30, respectively, and the fourth and fifth inputs of the path calculation unit of parameters 9, the output of the angular discriminator 8 is connected to the first input of the third key 28, the output of which is connected to the first input of the trajectory parameter calculation unit 9, the output of which is connected to the first input of the fourth key 29, the output of which is the output of the entire device, the second output of the transmitter 1 is connected to the second input of the transmitting antenna 2.

The transmitter 1 contains a frequency synthesizer 1.1, a first power amplifier 1.7, the output of which is the first output of the transmitter 1 and connected to the first input of the transmitting antenna 2, additionally introduced the first 1.3 and second 1.4 phase shifters, the inputs of which are connected to the output of the frequency synthesizer 1.1, and the outputs, accordingly, to the first inputs of the first 1.5 and second 1.6 key stages, the second inputs of which are connected to the output of the pseudo-random sequence generator 1.2, the output of the first key stage 1.5 is connected to the input of the first power amplifier ty 1.7, and the output of the second key stage 1.6 through the second power amplifier 1.8, the output of which is the second output of the transmitter 1, is connected to the second input of the transmitting antenna 2;

The first controlled matched filter 19 contains a delay line 19.1 with taps, the input of which is the first input of the first controlled matched filter 19, and its outputs are connected to the inputs of the block of controlled phase shifters of frequency tuning 19.2 corresponding to them by number, the control input of which is the third input of the first controlled matched filter 19, part of the outputs of the block of controlled phase shifters of frequency tuning 19.2 are connected to the inputs of the first adder of the first controlled matched filter 19.3, the output of which through the first controlled phase shifter of the azimuthal adjustment of the first controlled matched filter 19.6 is connected to the first input of the third adder of the first controlled matched filter 19.8, the other part of the outputs of the block of controlled phase shifters of the frequency tuning 19.2 is connected to the inputs of the second adder of the first controlled matched filter 19.4, the output of which is connected to the second input of the third adder of the first controlled matched about filter 19.8 through a series-connected phase shifter at π 19.5 and a second controlled azimuthal phase shifter of the first controlled matched filter 19.7, the output of which is the output of the first controlled matched filter 19, control inputs of the first 19.6 and second 19.7 controlled phase shifter of the azimuthal adjustment of the first controlled matched filter 19 connected to its second entrance;

The matched filter block 23 contains a delay line with taps 23.1, the input of which is the input of the matched filter block 23, and the outputs are connected to the N inputs of the frequency-shifting blocks of the frequency setting 23.2.1, ..., 23.2.i, ..., 23.2.N part of the outputs of which are connected to the N inputs of the first adders 23.3.1, ..., 23.3i, ..., 23.3.N corresponding to them according to the number, the outputs of which are connected to the first blocks of phase shifters corresponding to the number N to the M direction 23.6.1, ... 23.6 .i, ... 23.6.N, the other part of the outputs of each of the N blocks of the phase shifter of the frequency setting 23.2.1, ..., 23.2.i, ..., 23.2.N is connected to the inputs of the second adders 23.4.1, ..., 23.4.i, ..., 23.4.N corresponding to them by number, the output of each through the corresponding phase shifter to "Π" 23.5.1, ..., 23.5.i, ..., 23.5.N are connected to the corresponding inputs of the second blocks of the phase shifter settings on the M directions 23.7.1, ..., 23.7.i, ..., 23.7.N, M outputs of each of the first blocks of phase shifters, the settings on the M directions 23.6.1, ..., 23.6.i, ..., 23.6.N are connected to the first inputs of the M two-input adders 23.8. (1,1) ÷ 23.8. (1, M) corresponding to them by number , ..., 23.8. (I, 1) ÷ 23.8. (i, M), ..., 23.8. (N, 1) ÷ 23.8. (N, M), the second inputs of each of which are connected to the corresponding outputs of the second blocks of phase shifters of tuning in M directions 23.7.1, ..., 23.7 .i, ..., 23.7.N, the outputs of each of which are connected to the inputs of M amplitude detectors 23.9. (1,1) ÷ 23.9. (1, М), ..., 23.9. (i, 1) ÷ 23.9. (i, M), ..., 23.9. (N, 1) ÷ 23.9. (N, M), the outputs of which are the outputs of the entire block of matched filters 23.

The transmitter 1 contains a number of blocks having a standard implementation option and can be performed, for example, as shown in [1].

The first 4, second 12 and third 17 blocks of phase shifters can be made as shown in [2].

Transmitting antenna 2 can be performed as shown in [3]. The receiving antenna 3 and the second receiving antenna 10 can be performed as shown in [4].

The first 6, second 7, third 13 and fourth 22 receivers can be performed as in [5].

The first key 25, the second key 26, the third key 28 and the fourth key 29 can be performed as shown in [6].

The control voltage generating unit 30 can be made on the basis of the 1986VE9x architecture microcontroller, as shown in [7]. The first adder 4, the second adder 5, the third adder 12 and the fourth adder 21, as well as the first 19.3, second 19.4 adders of the first controlled matched filter and the first 20.3, second 20.4 adders of the second controlled matched filter can be performed, as shown in [8].

The matched filter 14, the first detector 15, the unit for calculating ΔR of the distance difference 16, the unit for calculating the path parameters 9; the first controlled matched filter 19, the angular discriminator 8, the second controlled matched filter 20, the matched filter block 23, the maximum selection unit 24, the second detector 27 can be performed on digital elements, as shown in [9].

The inventive device implements the polarization principle of separation of direct and reflected by the target signals and uses as the emitted signal phase-shifted (FM) signal with space-time (PV) encoding either in the form of a pseudorandom sequence (PSP), or in the form of pulsed radiation of a complex FM signal.

The device operates as follows: the receiving position (Fig. 1) is at a known distance L and the direction relative to the transmitting position. To determine the coordinates of the target (C) in the inventive device, its angular coordinates are measured: α - azimuth C relative to the transmitting position, β - azimuth C relative to the receiving position, these angles are measured relative to the line connecting the position. An assessment is also made of F _dΣ and the distance difference ΔR = R ₁ + R ₂ -L, R ₁ is the distance between C and the transmitting position, R ₂ is the distance between C and the receiving position. The indicated parameters are evaluated at the receiving position by the signals reflected from the C without the use of the extrapolation method, and practically for one received pulse with pulsed radiation or for one SRP period with continuous radiation.

Evaluation of β at the receiving position is performed by the standard monopulse algorithm, the distinguishing feature of which is the adjustment of the parameters of the matched filters 19 and 20 in the receiving channels according to the estimates of α and F _d .

Estimation of α is based on the use of P-V emitted signals. P-V emitted signals are signals that cannot be represented as the product of the time function (signal generated by the transmitter) and the spatial variable function (radiation pattern of the transmitting antenna). The formation of the emitted P-V signal on the example of a seven-element Barker code is shown in (Fig. 3a, b).

The P-V signal is formed by changing the position of the phase center of the transmitting antenna 2 when the FM signal is emitted (Fig. 2). For this, the fabric of the transmitting antenna 2 is divided into two identical sublattice parts, each of which has its own input A1 and A2, as shown in FIG. 3a. Elementary pulses of a signal having an initial phase of the time code (VC) equal to "0" are removed from the first output of transmitter 1 and emitted by the A1 sublattice, and pulses with an initial phase of VC equal to "π" are removed from the second input of the transmitter 1 and emitted by A2 sublattice. The choice between sublattices when emitting individual elements of the FM signal is carried out in accordance with a given angular code Ki (where i = 1 ... Nk), Nk is the number of elementary pulses making up the FM signal, the elements of which can take the values "+1" and "-1" . At Ki = + 1, the elementary momentum of the FM signal is emitted by the A1 sublattice, while the A2 sublattice does not emit radiation. At Ki = -1, the elementary momentum of the FM signal is emitted by the A2 sublattice, and the A1 sublattice does not emit.

где Δϕ - набег фазы, отсчитываемый от середины передающей антенны 2, D - расстояние между фазовыми центрами подрешеток А1 и А2 (база), α - угловая координата цели относительно равносигнального направления (РСН), λ - длина волны.As a result of such radiation, the function of the intrapulse phase modulation will depend on the direction α to the target. In FIG. 3b shows the signals emitted in the equal signal direction (RSN) and in the direction deviated by an angle α. Thus, the function of the intrapulse phase modulation of the signal radiated in the direction α will have the law of alternating the initial phases not “0” and “π”, but “0 + Δϕ” and “π-Δϕ”, where Δϕ is defined as

where Δϕ is the phase shift counted from the middle of the transmitting antenna 2, D is the distance between the phase centers of the A1 and A2 sublattices (base), α is the angular coordinate of the target relative to the equal-signal direction (RSN), λ is the wavelength.

Taking into account the additional phase increment after reflection from the target, the emitted signal can be written as

where p _s is the power of the emitted signal, F (α) is the directivity pattern (BH) of the transmitting sublattice A1 or A2, u (t) is the amplitude modulation function, and _i are VK elements (the value +1 corresponds to the initial phase equal to "0", the value -1 corresponds to the initial phase equal to "π"), rect (t) is the unit amplitude pulse of duration τ ₀ , τ ₀ is the duration of the ith elementary symbol of the code, ƒ ₀ is the frequency of the carrier wave, θ ₀ is the initial phase of the FM signal, K _i is the angular code (takes the values ± 1), ϕ (α) is the phase incursion, depending on the propagation direction of the emitted signal α.

The dependence of the phase structure of the signal on the angular position of the target makes it possible to construct a single-pulse meter of angular coordinates even with single-channel reception.

In the inventive device, the signals supplied to the first and second inputs of the transmitting antenna 2 are formed in the transmitter 1 (Fig. 2). To do this, the frequency synthesizer 1.1 generates a continuous sinusoidal oscillation with a radiation frequency that is fed to the inputs of the first 1.3 and second 1.4 phase shifters. Sinusoidal signals taken from the outputs of these phase shifters differ in phase by "π". The formation of the parts of the SRP supplied to the first and second inputs of the transmitting antenna 2 is performed using the generator SRP 1.2, the first 1.5 and second 1.6 key stages. The PSP 1.2 generator generates a sequence of pulses of duration τ ₀ each with polarities +1 or -1, the position of which corresponds to the positions of the elementary pulses of the PSP with the initial phase “0” and “π”. The duration τ _{0 of} pulses "+1" and "-1" determines the duration of the elementary radio pulses of the SRP or complex pulses of the FM signals during pulsed radiation of the transmitting antenna 2 and is set by the necessary value of the resolving power of the emitted signals in range δR.

When a second pulse of positive polarity +1 acts on the second input of the first key stage 1.5, this stage opens for a time τ ₀ and through it the PSP radio pulses with the initial phase “0” and duration τ ₀ pass to the input of power amplifier 1.7. The positive polarity pulses operating at this time close the second key stage 1.6 and a sinusoidal voltage having the phase “π” is not supplied to the input of the second power amplifier 1.8. Thus, when the first half of the transmitting antenna 2 is emitted pulses PSP or complex FM pulse with an initial phase of "0", the second half of the transmitting antenna 2 does not emit signals.

When the second input stage has 1.6 1.6 negative-polarity pulses operating at the second input of the pulse removed from the output of the PSP 1.2 generator, this stage is open, and the first stage 1.5 is closed. Therefore, at the moment of action of polarity pulses “-1”, a sinusoidal voltage with an initial phase “π” passes through the second key stage 1.6. These radio signals are amplified by a second power amplifier 1.8 and are supplied to the second input of the transmitting antenna 2 and radiated by its second half.

Thus, the transmitting antenna 2 together with the transmitter 1 form a P-V emitted signal, in which the law of intrapulse phase modulation depends on the direction of radiation. When such a signal is reflected, information about the angular position of the target α is encoded in its time parameters (in the law of phase modulation), and, therefore, can be extracted using a set of time filters that are consistent with a set of discrete directions of the irradiated sector α _i .

Transmitting antenna 2 emits vertical polarization signals. The orientation of the equal signal direction (RSN) of the transmitting antenna 2, in which the phase modulation of the PV signal has the law "0", "π", is directed to the receiving position.

To separate the direct signal and reflected from the target, their polarization differences are used. The signal emitted by the transmitting antenna 2 has a vertical polarization and stores it when passing directly to the receiving position (direct signal), and reflected from the target will have both vertical and horizontal polarizing components.

A direct vertical polarization signal is received by a receiving antenna 3 tuned to receive vertical polarization signals, and a second receiving antenna 10 tuned to receive horizontal polarization signals receives signals reflected from the target on the horizontal polarization.

As a result, the direct vertical polarization signal does not enter the channel for estimating the coordinates α, β, ΔR, F _{d of the} target, since the second receiving antenna 10, tuned to receive horizontal polarization signals, does not pass these signals. Thus, on the receiving side there are: a channel for processing a direct signal of vertical polarization and a channel for processing signals reflected from the targets of horizontal polarization, in which there is no direct signal.

The signal passing directly from the transmitting position to the receiving vertical polarization (direct signal) is received by the elements of the receiving antenna 3 and fed to the inputs of the first block of the phase shifter 11, the phase shifts in which have such values at which the output antenna of the receiving antenna is formed at the output of the third adder 12, the maximum of which sent to the transmitting position. PSP signals during continuous emission or FM pulses of pulse signals during vertical polarization pulse emission with intrapulse phase modulation “0” and “π” are removed from the output of the third adder 12, amplified and subjected to frequency filtering by the third receiver 13, after which they are supplied to the matched filter 14. In accordance with the above condition for matching the RSN of the transmitting antenna 2 with the direction to the receiving position, the parameters of the matched filter 14 are determined by the time code of the emitted signals, which ing determines the sequence of elementary pulses of duration τ ₀ from the initial phases of "0" and «π», constituting period CAP during continuous radiation law or phase modulation of the radiated FM composite signal.

The signals from the output of the matched filter 14 are fed to the input of the first detector 15. When the threshold selected in accordance with the set probability of false alarm detection of the direct signal is exceeded, the signal of the detection decision γ _B is removed from the output of the first detector 15. Coming to the first input of the calculation unit ΔR 16, the detection signal γ _B starts the counter, which was previously in the reset state.

а также обнаружитель этого сигнала.The channel for processing the horizontal polarized signal reflected from the target contains meters of the target angle relative to the transmitting position, the target angle relative to the receiving position, and the value

as well as a detector for this signal.

The signals reflected by the target have both vertical and horizontal polarizing components arrive at the second receiving antenna 10 tuned to receive horizontal polarization signals. Therefore, the direct signal of vertical polarization by the second antenna 10 is not received, which allows you to separate the signal reflected from the target from the signal passing directly from the transmitting position to the receiving one. The received signals from the outputs of the elements of the second antenna 10 are supplied to the inputs of the second 17 and third 18 blocks of phase shifters corresponding to them by number. The phase shifts set by the phase shifters are chosen so that at the outputs of the first 4 and second 5 adders, amplitude directivity patterns f (β + β ₀ ) and f (β-β ₀ ) are formed with matching phase centers with a spacing of their maxima in angle β by + β ₀ and -β ₀ relative to the RSN, which coincides with the direction to the transmitting position. At the outputs of the first 4 and second 5 adders, two MDs are formed which are used for monopulse measurement of the angular coordinate of the target relative to the receiving position by angular discriminator 8.

To detect the signal reflected from the target received at the horizontal polarization, the total pattern is formed by adding the signals in the fourth adder 21, taken from the outputs of the first 4 and second 5 adders. Received at the output of the fourth adder 21, the signals reflected from the target are amplified by the fourth receiver 22 and fed to the second detector 27 of horizontal polarization signals. The signals received from the target have a phase change law, which depends both on the time code generated by the PSP and taken from the output of the PSP 1.2 generator of transmitter 1, and on the direction α in which the target is located through the phase shift ϕ (α), as well as from the Doppler phase advance Δϕ _d at the elementary pulse duration τ ₀ of which the PSP or complex FM pulse consists. Thus, the signal received from the target at the output of the total DN is a function of such information parameters as α, β, and F _d . These parameters, along with the L values and the ΔR estimate, are used to determine the location of the target in the block for calculating the path parameters 9. The values of all these parameters are unknown in advance and represent random variables to be estimated.

With unknown information parameters of the received signals, the detector is constructed according to a multi-channel scheme. Each channel is configured to receive signals with some specific values of unknown parameters and contains either a correlator with a reference signal containing these specific parameters, or a matched filter with an impulse response corresponding to the selected values of these parameters and an amplitude detector.

The horizontal polarization signals received from the target by the second receiving antenna 10 have unknown phase intrapulse modulation values of "0 + Δϕ (α) + iΔϕ _d " and "π-Δϕ (α) + iΔϕ _d " (i = 1 ÷ (N _K -1) , N _K is the number of elementary pulses making up the SRP or FM signal), which depends both on the azimuth of the target α relative to the RSN of the transmitting antenna 2 and on the value of the Doppler phase addition iΔϕ _d depending on F _d . Therefore, the block of matched filters 23 is constructed according to the scheme of a set of filters matched with a set of M tuning points for sensing angles that cover the entire irradiated sector Δα from α _min to α _max with a step of δα. At each point of the angular tuning α _i , a set of matched filters is formed with tuning values F _dj (j = 1 ÷ N) covering the range of expected frequency shifts in increments of δF _d from F _dmin to F _dmax .

- число точек настройки по углу α, a для каждого направления

- точек настройки по доплеровской частоте.Thus, the matched filter block (SF) 23, consists of K filters K = N⋅M, where

- the number of adjustment points along the angle α, a for each direction

- Doppler frequency tuning points.

An analog implementation of the SF unit 23 is shown in FIG. 4, and the implementation of its j-th tuning channel by F _dj and M tuning points by angle α for the seven-element Barker code in FIG. 5.

The detected signals recorded from the outputs of the K filters are fed to the K inputs of the maximum selection block 24, which determines the filter number at the output of which the signal reaches its maximum amplitude.

и

истинных параметров α и F_д. Точность оценки будет определяться отношением сигнал-шум и шагом дискретизации δα по углу α и δF_д по значениям доплеровской частоты F_д.The signal reaches the maximum amplitude at the output of the filter for which the value of the angle α _i and the Doppler frequency F _dj are closest to the true values of these parameters in the signal received from the target. The setting values of this filter α _i and F _дi are taken as estimates

and

true parameters α and F _d . The accuracy of the estimate will be determined by the signal-to-noise ratio and the sampling step δα in the angle α and δF _d in terms of the Doppler frequency F _d .

и

соответствующие значениям настройки фильтра с максимальным входным сигналом, поступают на первый и второй входы блока выработки управляющих напряжений 30 соответственно и на четвертый и пятый входы блока вычисления траекторных параметров 9.The maximum amplitude signal from the third output of the maximum selection unit 24 is supplied to the second detector 27. When the threshold is exceeded in the second detector 27, the detection signal γ _g opens the first 25, second 26, third 28 and fourth 29 keys. Through the open first 25 and second 26 keys evaluation

and

corresponding to the filter settings with the maximum input signal, are supplied to the first and second inputs of the control voltage generation unit 30, respectively, and to the fourth and fifth inputs of the trajectory parameter calculation unit 9.

и

Для этого в блоке выработки управляющих напряжений 30 по оценкам

и

вырабатываются управляющие настройкой фазовращателей в первом 19 и втором 20 управляемых согласованных фильтрах напряжения, которые подаются на вторые и третьи входы первого 19 и второго 20 управляемых согласованных фильтров. Вариант аналоговой реализации управляемых СФ 19 и 20 приведены на фиг. 6а, б для ФМ сигналов без уточнения закона изменения фаз в принимаемом сигнале, а на фиг. 7 приведена реализация одного из управляемых СФ для ФМ сигнала - семиэлементного кода Баркера, приходящего с направления α со сдвигом по частоте F_д. Амплитуды сигналов на входах первого 19 и второго 20 управляемых согласованных фильтров, определяются, среди ряда прочих факторов, значениями коэффициентов направленности ДН приемных каналов, значения которых зависят от угла цели β. Сигналы с выходов первого 19 и второго 20 управляемых согласованных фильтров поступают на первый и второй входы углового дискриминатора 8 соответственно. Снимаемая с выхода углового дискриминатор 8 оценка

через открытый при срабатывании второго обнаружителя 27 третий ключ 28 подается на первый вход блока вычисления траекторных параметров 9.The angle β is estimated by a two-channel single-pulse amplitude meter. To this end, the signals taken from the outputs of the first 4 and second 5 adders are amplified by the first 6 and second 7 receivers and fed to the first inputs of controlled matched filters 19 and 20, respectively. To maximize the signal-to-noise ratio, these filters are adjusted to the phase structure of the received signals by parameter estimates

and

To do this, in the block generating control voltages 30 according to estimates

and

the control settings of the phase shifters in the first 19 and second 20 controlled matched voltage filters are generated, which are supplied to the second and third inputs of the first 19 and second 20 controlled matched filters. A variant of the analog implementation of controlled SFs 19 and 20 is shown in FIG. 6a, b for FM signals without specifying the law of phase change in the received signal, and in FIG. Figure 7 shows the implementation of one of the controlled SFs for the FM signal — the seven-element Barker code arriving from direction α with a frequency shift of F _d . The amplitudes of the signals at the inputs of the first 19 and second 20 controlled matched filters are determined, among other factors, by the values of the directivity coefficients of the receiving channels, the values of which depend on the target angle β. The signals from the outputs of the first 19 and second 20 controlled matched filters are fed to the first and second inputs of the angular discriminator 8, respectively. Corner Discriminator 8

through open when the second detector 27 is triggered, the third key 28 is supplied to the first input of the trajectory parameter calculation unit 9.

In the block for calculating the trajectory parameters 9, the range is calculated relative to the receiving position in a triangulation manner. From the triangle RC ^/ T (Fig. 8) by the sine theorem we express:

Прямоугольные координаты определим относительно позиций R и Т какThen

Rectangular coordinates are defined relative to the positions of R and T as

Considering that with another measured parameter in the geometry of the problem presented in FIG. 8 is the total range:

Then, taking into account (2), we obtain the value of the target’s flight altitude in the form:

In FIG. Figure 9 shows the RMS values for determining the target’s flight altitude at a base value of L = 50 km, the target performs a straight flight at an altitude of 5000 m perpendicular to the base line at a speed of 200 m / s with initial coordinates X = 20 km, Y = 15 km. The standard deviations for determining the target height were obtained with: standard deviations for determining angular coordinates σ _p = 0.1 deg., _Standard deviations for determining the total range σ _RΣ = 10 m.

In FIG. 10 shows the RMS values for determining the target’s flight altitude under the same conditions, but the target flies at an angle of 60 degrees to the base line.

In FIG. Figure 11 shows the standard deviation for determining coordinates when the target is flying parallel to the X axis (base line) at Ho = 45,000 m, Yo = 5,000 m. Under such conditions, using a prototype device, determining the height is impossible, since it is impossible to extrapolate the total Doppler frequency to the base line.

In FIG. Figure 12 shows the standard deviation for determining coordinates when the target is flying parallel to the X axis (base line) at Хо = 45000 m, Yo = 500 m. Under such conditions, using a prototype device, determining the height is impossible, since it is impossible to extrapolate the total Doppler frequency to the base line.

The second input of the block for calculating the trajectory parameters 9 from the output of the block for calculating ΔR 16 receives an estimate of the difference in the distances of the signals ΔR directly and reflected from the target, the value of which is calculated by the difference in the detection times of a signal passing along a straight path from the transmitting position to the receiving one and equal to the known value L and the signal reflected from the target and the distance R ₁ + R ₂ > L, where R ₁ and R ₂ are the distances from the transmitting position to the target and from the target to the receiving position, respectively.

In the case of R ₁ + R ₂ = L means that the target flies strictly along the line connecting the transmitting and receiving positions. In this case, the azimuthal and elevation angles with respect to the transmitting and receiving positions are the same and equal to zero. Among the many possible flight paths of targets, the probability of the appearance of any particular path is zero. This assumption is most relevant to the appearance of the target's flight path strictly in a straight line connecting the positions. Any other flight paths of the target, for example, parallel to the line connecting the positions, will have non-zero or azimuthal or elevation coordinate of the target, or both.

Therefore, the ΔR value is almost always ΔR ≠ 0. The accuracy of the ΔR estimate is determined by the accuracy of fixing the moments of detection of the direct and reflected signals and the range resolution of the continuous transmission bandwidth or single FM signals used by the transmitting position. Also, accuracy depends on the signal-to-noise ratio, which is especially characteristic of a signal reflected from a target. In the direct signal receiving channel, the signal-to-noise ratio will be much larger, due to the shorter propagation distance, the absence of fluctuation noise of the ESR of Ts. When the trajectory of Ts moves closer to the line connecting the transmitting and receiving positions, the ΔR value will decrease, and the signal-to-noise ratio in the receiving channel of the horizontal polarization component increases due to the increase in the lumen EPR and the maximum values of the directivity gain of the transmitting 2 and second receiving 10 antennas. An increase in the EPR lumen when approaching the angular coordinates of Ts to the RSN of the transmitting 2 and second receiving 10 antennas causes not only an increase in the signal-to-noise ratio, but also minimization of the variance of the estimate of the angular coordinates, which allows one to obtain high accuracy in estimating the location of Ts for almost any flight path within angular sector irradiated by the transmitting antenna 2.

As a result of the above factors, the accuracy of the target position estimation will be high for almost any flight paths within the angular sector of the transmitting antenna.

The blocks used in the inventive device for measuring the angular coordinates of Ts α and β, the distance difference ΔR and the values of F _d solve the problem of estimating the location of Ts for one received pulsed FM reflected signal or for one period of continuous SRP without extrapolating its path. This circumstance eliminates the delay in obtaining an estimate of the location of C, as it does not require extrapolation of the trajectory of the target, as required in the prototype device.

The use of a complex emitted FM signal with two types of encoding - temporal and angular - makes it difficult to detect codes, which means the detection of such signals and the setting of leading interference, which leads to an additional technical result, because The claimed device has a greater stealth and greater noise immunity inherent to complex FM signals, and, therefore, greater noise immunity than the prototype device.

SOURCES OF INFORMATION

1. Shahgildyan V.V. and other radio transmitting devices, M .: Radio and communications, 203.- 560 p. Page 512 images 19 b.

2. Panasyuk, Yu.N. Devices of superhigh frequencies. / Yu.N. Panasyuk, A.P. Pudovkin. - Tambov: Publishing House of FSBEI HPE "TSTU", 2015. - 80 p. Page 49. Fig. 2.44.

3. A guide to the basics of radar technology. Ed. Druzhinina V.V. M.: Military publishing house, 1967. 776 p. p. 165. Fig. 4.48.

4. Bakulev P.A., Radar systems. - M .: Radio engineering, 2004, 320 s. 11.12 p. 261.

5. Designing radio receivers under. ed. Sivers A.P. M .: “Owls. Radio ”, 1976, p. 68 2.25, 485 s.

6. Gusev V.G., Gusev Yu.M. Electronics and microprocessor technology: Textbook. for universities. - M .: Higher. school, 2008. - 798 p.: p. 512. Fig. 10.9).

7. Ogorodnikov, I.N. Microprocessor technology: introduction to Cortex-M3: textbook. allowance / I.N. Ogorodnikov. - Yekaterinburg: Publishing House Ural. University, 2015 .-- 116 p. Page 35 Figure 2.2.

8. Veselov GI, Egorov EN, Alekhin Yu.N. and other microwave electronic devices. Ed. Veselova G.I., Moscow: Higher School, 1988 .-- 280 p. fig. 3.27 p. 74.

9. Ogorodnikov, I.N. Microprocessor technology: introduction to Cortex-M3: textbook. allowance / I.N. Ogorodnikov. - Yekaterinburg: Publishing House Ural. University, 2015 .-- 116 p. Page 35 Figure 2.2.

Claims (4)

1. A device for determining the motion parameters of the target, containing a transmitting position, consisting of a transmitter, the output of which is connected to the input of the transmitting antenna, and located at a distance from the radiation source, a receiving position, consisting of a receiving antenna, the first and second adders, the outputs of which are connected respectively with the inputs of the first and second receivers, as well as an angular discriminator and a trajectory parameter calculation unit, characterized in that the device additionally includes: a second receiving antenna, followed by no connected first block of phase shifters, a third adder, a third receiver, the matched filter, the first detector and the calculating unit ΔR, whose output is connected to the second input of trajectory parameters calculation block, the third input of which is the input supply range values L, where ΔR = R ₁ + R ₂ -L, R ₁ - distance between the target and the transmitting position, R ₂ - distance between the target and the receiving position, L - known distance between the receiving position and transmitting position input unit of the first phase shifters are connected to the outputs of receive antennas s, the second and third blocks of phase shifters, the inputs of which are connected to the outputs of the second receiving antenna, and the outputs are connected to the inputs of the first and second adders, the first and second controlled matched filters, the first inputs of which are connected respectively to the outputs of the first and second receivers, and the outputs are connected to the inputs of the angular discriminator, the fourth adder, the fourth receiver, the matched filter unit and the maximum selection unit, the first and second outputs of which are connected to the first inputs of the first and second keys, serially connected the third output is connected to the input of the second detector, the output of which is connected to the second inputs of the first, second, third, fourth keys and the second input of the calculation unit ΔR, and the first and second inputs of the fourth adder are connected to the outputs of the first and second adders, respectively, the control voltage generation unit, the first output of which is connected to the second inputs of the first and second controlled matched filters, the second output is connected to the third inputs of the first and second controlled matched filters, the output the first and second keys are connected to the first and second inputs of the control voltage generation unit, respectively, and the fourth and fifth inputs of the path parameter calculation unit, the output of the angular discriminator is connected to the first input of the third key, the output of which is connected to the first input of the path parameter calculation unit, the output of which is connected to the first input of the fourth key, the output of which is the output of the entire device, the second output of the transmitter is connected to the second input of the transmitting antenna. 2. A device for determining the target motion parameters according to claim 1, characterized in that the transmitter contains a frequency synthesizer, a first power amplifier, the output of which is the first output of the transmitter and connected to the first input of the transmitting antenna, the first and second phase shifters, the inputs of which are connected to the output of the frequency synthesizer, and the outputs, respectively, to the first inputs of the first and second key stages, the second inputs of which are connected to the output of the pseudo-random sequence generator, the output of the first key stage is connected It is connected to the input of the first power amplifier, and the output of the second key stage through the second power amplifier, the output of which is the second output of the transmitter, is connected to the second input of the transmitting antenna. 3. A device for determining the parameters of the target’s movement according to claim 1, characterized in that the first controlled matched filter contains a delay line with taps, the input of which is the first input of the first controlled matched filter, and its outputs are connected to the inputs of the block of controlled phase shifters corresponding to them by number frequency tuning, the control input of which is the third input of the first controlled matched filter, some of the outputs of the block of controlled phase shifters of the frequency tuning are connected to the corresponding The number of inputs of the first adder of the first controlled matched filter, the output of which through the first controlled phase shifter of the azimuthal tuning of the first controlled matched filter is connected to the first input of the third adder of the first controlled matched filter, the other part of the outputs of the block of controlled phase shifters of the frequency tuning is connected to the inputs corresponding to them by number the second adder of the first managed matched filter, the output of which is connected to the second input the third adder of the first controlled matched filter through a serial connected phase shifter to “π”, and the second controlled azimuthal phase shifter of the first controlled matched filter, the output of which is the output of the first controlled matched filter, the control inputs of the first and second controlled azimuthal phase shifters of the first controlled matched filter are connected to his second entrance. 4. A device for determining the parameters of the target’s movement according to claim 1, characterized in that the matched filter block contains a delay line with taps, the input of which is the input of the matched filter block, and the outputs are connected to the inputs of the N blocks of phase shifters of the frequency setting matching them by number, part the outputs of which are connected to the N inputs of the first adders corresponding to them by number, the outputs of which are connected to the first blocks of the setup phase shifters corresponding to them by number N in the M direction, the other part of the outputs of each of the N blocks of phase-shifting frequency shifters connected to the inputs of the second adders corresponding to them by number, the output of each of which through the corresponding phase shifter to “π” are connected to the inputs of the second blocks of the phase shifting tuners corresponding to them by number in M directions, M outputs of each of the first blocks of the tuning phase shifters in M directions are connected to the first inputs of the M two-input adders corresponding to them by number, the second inputs of each of which are connected to the outputs of the second x phase shifters tuners on M lines, each of which outputs are connected to inputs of M amplitude detectors, the outputs of which are the outputs of all matched filter unit.

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