RU2581774C1 - Information transmission method and system for its implementation - Google Patents

Abstract

FIELD: information technology.

SUBSTANCE: invention relates to method and system for transferring information. That is ensured by converting a binary code in two sequences of logic ternary code with symbols S₀, S₁, S₂ and T₀, T₁, T₂, whereupon at the first stage of modulation the first sequence of signals S₀, S₁, S₂ are in the form of amplitude-pulse modulation (APM₃), and the second T₀, T₁, T₂ - in the form of width-puls modulation (WPM₃). Then at the second stage of modulating signal transmitted via communication channel, APM₃ is converted to frequency modulation (FM₃), and amplitude of frequency-modulated oscillations is set in compliance with values ternary code symbols S₀, S₁, S₂. Note here that three fixed durations of WPM₃, are converted to binary phase modulation $$F{M}_2^{(3)},$$

whereupon changing WPM duration the carrier phase with combined modulation FM₃+AM₃ is changed to 180°. At the receiving side for demodulation of signal generated at the transmitting side, apart from frequency and phase demodulators in each channel allocating frequency components of the received signal, the amplitude demodulator is used, the obtained results of amplitude demodulation are compared with data recieved by frequency and phase demodulators.

EFFECT: technical result consists in improvement of reliability of transmitted information.

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Description

The invention relates to telemetry, communication technology and can be used in data transmission systems over communication channels. Its use allows to increase the reliability of information transfer without introducing structural redundancy in transmitted messages, to detect errors occurring during transmission, both single and multiple, to increase the speed of information transfer.

A known method of transmitting information ([1], RF patent No. 2115172 "Method of transmitting information and a device for its implementation", priority of the invention of 03/10/1993, IPC G08C 19/28, published on 10.07.1998, bulletin No. 19) which consists in collecting signals from message sources, synchronizing them in time, generating a compressed signal from synchronized collected signals, generating a signal of the first carrier frequency, phase manipulating the signal of the first carrier frequency with a compressed signal, transmitting the modulated signal over the communication channel, exc characterized in that a second carrier frequency signal is generated, a periodic sequence of a meander-type pulse signal is generated with a pulse duration half the minimum pulse width of the compressed signal, phase manipulation of the second carrier frequency signal with a compressed signal is performed, after which the modulated signal to be transmitted via the communication channel is formed signal by frequency manipulation of phase-shifted signals of the first and second carrier frequencies by a pulse-phase-shift signal periodic sequence.

In the invention [1] after synchronization and compression of messages, not one but two binary video signals are generated with different encoding logic. Moreover, according to the law of one of the binary logics represented by high and low voltage levels, phase manipulation is performed, and according to the law of another binary logic, frequency modulation is performed.

Its disadvantage lies in the limited detection and correction of information transmission errors. This is due to the fact that the redundancy of the transmitted information is created only at the level of radio signals by using several types of modulation of the carrier frequency. In this case, the traditional level of error-correcting coding is not used at the level of data representation with binary or multi-base code.

All modern information transfer technologies include noise-resistant coding of transmitted information. However, the traditionally formed idea of noise-resistant coding is associated with noise-resistant codes, in which the required redundancy is formed at the level of binary symbols “0” and “1” ([2], Morelos-Zaragoza R. The art of noise-resistant coding. Methods, algorithms, application. - M .: Technosphere, 2006. - 320 p.). The modern concept of error-correcting coding also involves the use of distributed technology of error-correcting coding, which is understood as the use of coding in various paths of the formation and transmission of information ([3], Kukushkin S. S. Finite-field theory and computer science: volume 1 Methods and algorithms, classical and non-traditional, based on the use of the constructive remainder theorem. - M: Ministry of Defense of the Russian Federation, 2003. - 281 p.).

One of such solutions is proposed in the invention ([4], RF patent No. 2480840), which in the proposed method was used as a prototype. The method of transmitting information [4], consists in collecting signals from message sources, synchronizing them in time, generating a compressed signal from synchronized collected signals, generating a carrier frequency signal, modulating the carrier frequency signal with a compressed group signal based on the generated video code, transmitting the modulated signal over the channel communication. It differs from other analogs in that for transmitting information, the binary video signal of service and information messages, after being compressed, is converted into a substitute ternary logical error-correcting code, which is generated on the basis of the adopted logical coding rule, and on the basis of the adopted logical coding rule at the first stage of binary code transformations form two components of the modulating video signal designed to modulate the carrier frequency of the transmitted signal, each of which has three coding symbols conventionally defined as “S ₀ ” and “T ₀ ”, “S ₁ ” and “T ₁ ” “S ₂ ” and “T ₂ ”, the first modulating component of the converted first tribasic video signal containing the characters “S ₀ ” , "S ₁ " and "S ₂ ", represent in the form of pulse-amplitude modulation, and the second modulating component of the video signal with symbols of the three-basic code "T ₀ ", "T ₁ " and "T ₂ ", where T ₀ is the duration of one character the source binary code is used for pulse width modulation of the second video signal, while in the second stage of the transformations associated associated with the modulation of the carrier of the transmitted signal, the pulse-amplitude modulation of the generated video signal is converted, for example, into the frequency modulation of the signal with three fixed values of the frequency of the transmitted signal "f ₂ = f _n -Δf _d ", "f ₁ = f _n + Δf _d " and "F ₀ = f _n ", where f _n is the value of the carrier frequency of the signal, a Δf _d is the value of the frequency deviation, and the second component of the generated video signal is used for phase modulation of the transmitted signal by changing the phase by 180 ° at the boundaries of time intervals corresponding to ternary from the characters "T ₀ ", "T ₁ " and "T ₂ ".

Also in the prototype method [4], a video signal with a base of three (S _i , i = 0, 1, 2) is formed from a binary code, which leads to the use of a new one that is more economical with respect to binary codes (A _i , i = 0.1 ) the ternary information coding system, on the basis of which the spectrum of transmitted signals is compressed, by a sequence of generated ternary symbols, the signal transmitted via the communication channel is modulated using several types of different secondary modulation, with binary combinations (“00” and “11 ») Original follower awns binary symbols corresponding to a new symbol ternary «S _0" code, codewords starting binary baseband code ( "001" and "10") is replaced by the symbol ternary code «S _1" and remaining in the original sequence binary baseband code combinations type “101” unambiguously correspond to the symbol of the ternary code “S ₂ ”, on the receiving side when decrypting ternary symbols, conventionally designated as “S ₀ ”, “S ₁ ” and “S ₂ ”, the control of the uniqueness of the restoration of transmitted messages during reverse translation tr ary code into original binary code is produced based on checking the condition of coincidence of the last binary symbol "0" or "1" of the previous decryption of the received ternary symbol to a first symbol of "0" or "1" followed by the decryption, the existence of an error in the reception of ternary symbols «S ₀ "," S ₁ "and" S ₂ "are determined on the basis of a violation of this rule.

In addition, in the prototype method [4], the phase modulation of the transmitted signal is performed by changing the phase of the carrier of the transmitted signal at times that define the boundaries of the pulse duration of the generated tribasic code "T ₀ ", "1,5T ₀ " and "2T ₀ ", where T ₀ - the duration of the binary character "0" or "1" of the primary binary code.

The disadvantage of the prototype method [4] is that the possibility of simultaneous two-dimensional encoding with a ternary code and two-dimensional modulation of the video signal and the carrier frequency of the radio signal, implemented by the following parallel schemes:

and

where {A _i , i = 0,1} is the source binary code of the group signal, not fully used.

In addition, binary phase modulation (FM ₂ ) is widely used in digital data transmission systems, but it is replaced by other more economical modulation systems, for example, relative phase shift keying (OFM), and therefore it becomes urgent to establish conditions for matching their logical constructions that make it possible to establish their common properties, which are manifested during demodulation and decoding of signals using the proposed binary phase shift keying (FM ₂ ⁽³⁾ ), formed in accordance with the rule (2), and signals from the traditional OFM, which is used for transmission in some existing telemetry systems and information transfer systems.

It is known ([5], "Modern telemetry in theory and in practice / Training course", St. Petersburg: Nauka i Tekhnika, 2007. - 672 s, p. 139) that the advantage of OFM over traditional binary phase modulation (FM ₂ ) is concluded in a lower density of phase value changes by 180 °, while KIM ₂ -FM ₂ and KIM ₂ -OFM are characterized by almost the same specific energy consumption.

Also, when using KIM ₂ -OFM, it becomes possible to use a directly received OFM signal and its copy delayed by one clock cycle equal to the duration of one binary symbol of the source binary code when receiving a matched filter. As a result of this, when receiving information under interference conditions, they provide a 4-fold increase in the signal-to-noise ratio at the output of the quadratic demodulator (Fig. 1 (diagrams (1-4)). A similar demodulation algorithm has received a special name - “soft noise-resistant decoding” [2] to indicate fundamental differences from the traditional “hard noise-free decoding”, which is performed in the algebraic theory of noise-resistant coding based on check symbols ([6], Clark J., Jr., Kane J. Error correction coding side in digital communication systems./ Transl. from English. - M.: Radio and Communications, 1987. - 392 p.).

However, binary phase modulation (FM ₂ ⁽³⁾ ), which is used both in the prototype and in the present invention, has a fundamental difference from the traditional version of its application. It lies in the fact that (FM ₂ ⁽³⁾ ) is used to represent not two, as is customary in world practice, but three different code characters. In the prototype method and in the present invention, the symbols of the tribasic code are the durations of the primary signals with PWM corresponding to the symbols of the tribasic code {T ₀ , T ₁ = 1,5T ₀ , T ₂ = 2T ₀ }, while in the current practice of transmitting information binary phase modulation (FM ₂ ) is identified with binary codes represented by the symbols “0” and “1” ({A _i , i = 0,1} - see formalized notation (1), (2)). Thus, binary phase modulation (FM ₂ ⁽³⁾ ) is used to represent the characters of the non-binary (tribasic) code {T ₀ , T ₁ = 1,5T ₀ , T ₂ = 2T ₀ }, therefore it is classified as non-traditional replacement modulation types . But due to differences of this kind (FM ₂ ⁽³⁾ ) cannot be converted into traditional relative phase modulation (OFM) based on existing logical rules. In addition, there is no possibility of comparing the results obtained and the data obtained using the algorithms of “soft noise-free decoding” of relative phase modulation (OFM).

Therefore, there is a practical need to establish new logical relationships between the proposed binary phase modulation (FM ₂ ⁽³⁾ ) and traditional relative phase modulation (OFM).

In addition, the needs of existing practice, taking into account the new economic conditions, require that, on the one hand, all new information technologies are quickly implemented, which is often hindered by the basic technical solutions implemented in existing practice, and at the same time, the modernization of existing systems and systems should be minimum cost. In conditions of such contradictions, those technical solutions that require the introduction of a minimum of corrections at the hardware level in existing systems and telemetry systems are of particular importance. As a rule, traditional methods cannot be used to resolve such contradictions, so special relevance is felt in the search for various non-traditional reserves. Their basis is the establishment of new relationships, both logical and analytical, including between new types of modulation that appear during the transition from binary to a more economical logical ternary code, which forms the basis of the prototype invention ([4]).

The first conditional group of technical solutions using new reserves to improve the efficiency of information and telemetry support (ITO) for testing complex technical complexes (STK) are patents RU No. 2434301, No. 2434302, No. 2434303, No. 2434304, No. 2444066, No. 2445709, No. 2447492, No. 2457543 ([7]). But the new methods of structural-algorithmic transformations (SAPs) of the transmitted information that are implemented in them relate to informational sections of the formation of telemetry data using the unconventional representation of messages and signals by their residual images. The second group of methods closest to the proposed technical solution is represented by patents RU No. 2461888 ([8]), No. 2475861 ([9]), No. 248838 ([10]), in which the proposed structural-algorithmic transformations (SAP) are associated with modulation coding of transmitted information and signal modulation.

In terms of reverse SAP performed on the receiving side, the closest to the proposed method is patent RU 2475861 ([9]), the essence of which is that "... when receiving information, signals of the first and second carrier frequencies are simultaneously isolated, each of which is modulated phase by a digital group signal, form copies of the first and second carrier frequencies by local generators, which are tuned to the received carrier signals based on the generated corresponding mismatch signals, fill in the gaps associated with the transmission this is the time of another carrier frequency, by adding the carrier frequency signals of local generators of the corresponding frequency until the first and second information transmission frequencies are continuous in time, they are subjected to simultaneous phase demodulation, as a result of which direct and inverse copies of video signals with binary coding logic adopted for transmitting information are formed control the integrity and reliability of the transmitted messages based on the addition of the generated direct and inverse copies of the video signals with a logical and binary code levels adopted for transmitting information ... ”

The main technical result, the achievement of which the present invention is directed, is to increase the reliability of information transfer based on the transition from a binary code to its ternary code and establishing new logical relationships between signals with relative phase modulation (OFM) and signals with the proposed binary phase modulation ( FM ₂ ⁽³⁾ ).

This is achieved through the use of the following additional reserves to increase the efficiency of information transfer systems:

- additional in relation to the rules (1) and (2) amplitude modulation:

- establishing general logical relationships between the proposed binary phase modulation (FM ₂ ⁽³⁾ ), implemented in accordance with rule (2), and traditional relative phase modulation (OFM), which is used for transmission in existing telemetry systems and information transfer systems.

Using additional provision as an additional modulation step (3) allows a higher technical effect simultaneously use traditional relative phase modulation (RPM), and proposed a binary phase modulation (FM ₂ ^(3)), for example, when transferring redundant TMI flows in parallel radio channels, as well as the transmission of information recorded on board the controlled object storage devices (memory).

Thus, the main technical result is achieved by the fact that in a method of transmitting information, which consists in collecting signals from message sources, synchronizing them in time, generating a compressed signal from synchronized collected signals, generating a carrier frequency signal, modulating the carrier frequency signal with a compressed group signal based the generated video code, the transmission of the modulated signal over the communication channel, the binary video signal of service and information generated for the transmission of information After it is compressed, it is converted into a substitute ternary error-correcting code, which is formed on the basis of the adopted logical coding rule, and on the basis of the adopted logical coding rule, at the first stage of binary code transformations, two components of the modulating video signal are designed to modulate the carrier frequency of the transmitted signal, each of which has three coding symbol, conventionally defined as «S _0» and «T _0», «S _1" and «T _1», «S _2" and «T _2", the first modulating component f eobrazovannogo first tribasic video signal comprising characters «S _0», «S _1" and «S ₂ 'are in the form of pulse amplitude modulation, and the second modulating component of the video signal with symbols tribasic code« T ₀ »,« T ₁ "and" T ₂ "where T ₀ - the duration of one symbol original binary code is used for pulse width modulation of the second video signal, wherein the second phase transformation associated with the transmitted modulated carrier signal pulse amplitude modulation generated video Conv form a, for example, in frequency modulation with three fixed values of the frequency signal transmitted signal «f _n = f ₂ -Δf _d», «f _n = f ₁ + Δf _d" and «f ₀ = f _n" where f _n - value the carrier frequency of the signal, Δf _d is the value of the frequency deviation, and the second component of the generated video signal is used for phase modulation of the transmitted signal by changing the phase by 180 ° at the boundaries of time intervals corresponding to the ternary symbols "T ₀ ", "T ₁ " and "T ₂ " enter new steps of: at the transmitting side, the amplitude of the transmitted signal «f _n = f ₂ -Δf _d», «f ₁ = f + Δf _d »and« f ₀ = f _n ", also brought into conformity with the values of a pulse amplitude modulation symbols transmitted ternary« S ₀ "code,« S ₁ "and« S ₂ ", and for demodulating at the receiving side formed on the transmitting side of the signal, in addition to the frequency demodulator, made as narrow-band filters tuned to the frequencies "f ₂ = f _n -Δf _d ", "f ₁ = f _n + Δf _d " and "f ₀ = f _n ", and phase demodulators in each of the channels for allocating the frequency components of the received signal, use as an independent channel demodulation received with the amplitude demodulator, the results of the amplitude demodulation are compared with the data obtained by the frequency and phase demodulators, the comparison results are used to increase the reliability of receiving TMI.

The achievement of the main technical result also suggests that for demodulation on the receiving side of the combined modulation of a new type, which is a simultaneous change in frequency and amplitude in accordance with a three-basic code formed by the sequence of frequencies transmitted through the communication channel "f ₂ = f _n -Δf _d ", " f ₁ = f _n + Δf _d ”and“ f ₀ = f _n ”of the signal, which unambiguously correspond to the symbols of the three-basic code of the first type:“ S ₀ ”,“ S ₁ ”and“ S ₂ ”, the generated signal with frequency modulation three fixed values The frequency responses are additionally modulated using phase modulation with a 180 ° phase shift of the generated signal, which is produced with respect to the frequencies “f ₂ = f _n -Δf _d ”, “f ₁ = f _n + Δf _d ” and “f ₀ = f _n ", at times coinciding with the boundaries of the ternary symbols of the second type:" T ₀ "," T ₁ "and" T ₂ "having primary pulse-width modulation with duration values T ₀ , T ₁ = 1,5T ₀ , T ₂ = 2T ₀ , respectively, while the frequency amplitudes “f ₂ = f _n -Δf _d ”, “f ₁ = f _n + Δf _d ” and “f ₀ = f _n ” are unambiguously associated with the amplitudes of the symbols of the three code of the first type: “S ₀ ”, “S ₁ ” and “S ₂ ” at their primary amplitude-pulse modulation. Its distinctive feature lies in the fact that when receiving information, the carrier frequency signals are simultaneously distinguished not by two, as in the analogue of [9], but by three narrow-band filters that are tuned to the corresponding frequencies “f ₂ = f _n -Δf _d ”, “f ₁ = f _n + Δf _d ”and“ f ₀ = f _n ”, with the simultaneous formation of three parallel demodulation channels, in each of which the selected frequency is modeled in phase by a group signal formed on the transmitting side, a priori known forms in each of the parallel demodulation channels frequency «f ₂ = f -Δf _d »,« f _n = f ₁ + Δf _d "and« f ₀ = f _n "with predetermined amplitudes« S ₀ »,« S ₁ "and« S ₂ "of the local oscillator, arranged under the receiving signals of the frequency components" f ₂ = f _n -Δf _d ”,“ f ₁ = f _n + Δf _d ”and“ f ₀ = f _n ”, based on the corresponding mismatch signals between the frequencies of the received signal and the frequencies of the local generators, fill in the gaps associated with the transmission at this time other «f _n = f ₂ -Δf _d" of frequencies, «f _n = f ₁ + Δf _d" and «f _n = f _0" by adding local carrier signal generator frequency corresponding to the frequency and the amplitude the formation of time-continuous information transfer frequencies “f ₂ = f _n -Δf _d ”, “f ₁ = f _n + Δf _d ” and “f ₀ = f _n ” with preservation of the moments of phase change by 180 °, subject them to simultaneous phase demodulation as a result of which, for each of the three parallel demodulation channels, the results of frequency and phase demodulation are supplemented, each of which is presented in the form of direct and inverse copies of video signals with binary coding logic adopted for information transfer, integrity and reliability control is transmitted messages recovered during frequency and phase demodulation of the received signal based on pairwise addition of the generated direct and inverse copies of the video signals represented by the logical levels of the binary code received for information transfer, the result is compared with the results obtained by amplitude detection of the received signal.

The technical result, which involves the joint use of various methods of secondary modulation of video signals, as well as the determination of the conditions for their coincidence and comparability when transmitting duplicate streams of telemetric information, as well as data from a storage device, is achieved by the fact that in the proposed method, two video signals are generated from the binary code with a base (A _i , i = 0,1), and with a base of three (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ), parallel communication channels are used to transmit the generated two information streams, while as the main communication channel, use the traditional radio channel with relative phase modulation (OFM) of the video signal of the original binary group sequence of transmitted symbols (A _i , i = 0.1), and in the additional communication channel, which is used to transmit duplicate information, the signal is modulated by a sequence, consisting of formed ternary symbols (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ), using several types of different secondary modulation, for example, amplitude with a base of three, frequency with a base of three and phase with a base Two (FM ₂ ⁽³⁾ ), while the binary combinations (“00” and “11”) of the initial sequence of binary symbols correspond to the ternary code symbols “S ₀ and T ₀ ”, the code combinations of the original binary code of the group signal (“001” and “10”) are replaced by ternary code symbols “S ₁ and T ₁ ”, and the ternary code symbols “S ₂ and T ₂ ”, which are in the unambiguous correspondence, remain in the initial sequence of the binary code of the group signal of the code combinations of the form “101” side when decoding ternary symbols, conventionally designated as (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ), the control of the uniqueness of the restoration of transmitted messages during the reverse translation of the ternary code to the source binary code is carried out on the basis of checking the condition of coincidence of the last binary character "0" or "1" of the previous decryption of the received ternary character with the first character " 0 ”or“ 1 ”of the subsequent decryption, while the presence of an error in the reception of ternary symbols (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ) is determined both on the basis of violation of this rule, and by coincidence in time moments determined by the change of pulses periodically signal sequence starting binary symbol timing, phase values varying by 180 °, from the signals modulated using the relative phase modulation (RPM) of the original baseband signal sequence represented by a conventional binary code, and binary phase modulation (FM ₂ ^(3)), which was used in the transmission baseband signal, represented at the transmitting side logical error-correcting code symbols with base three (T _0, T ₁ and T ₂₎ using primary latitudinal is a pulsed modulation, with the integrity and authenticity of the received information is evaluated based on the alignment of the synchronous time-sequence data matches the phase changes by 180 ° when the proposed RPM and binary phase modulation (FM ₂ ⁽³⁾⁾ with the boundaries of the periodic signal sequence symbol synchronization binary code, which is restored when receiving a copy of the original encoding results of the television measurements received on the transmitting side, the absence of the listed matches is perceived as to the existence of errors which appeared in the transmission and reception of information.

The conversion algorithm that forms the basis of the present invention involves replacing the sequence of characters of the binary code A = {0,1}, composed of binary characters 0 and 1, the sequence of characters of the ternary code B = {S ₀ , T ₀ ; S ₁ , T ₁ , S ₂ , T ₂ }, consisting of three characters {S ₀ , T ₀ }; {S ₁ , T ₁ }; {S ₂ , T ₂ }, involves the following operations.

The generated group signal (4), presented in binary code, displayed, for example, by a sequence of the following form A _i = <10101000111100101> ₂ (i = 0.1) with the number of characters N ₁ = 17, is transferred to a new tribasic logical code: S ₀ ↔ ("00", "11"); S ₁ ↔ (“10”, “001”); S ₂ ↔ "101", which for simplicity of writing is represented only by S _i characters, using conditional upper and lower partitions (ℜ ₁ and ℜ ₂ ) of a given initial set of binary characters A _i . If we assume that the entire sequence of transmitted ternary symbols S _i (i = 0, 1, 2) is numbered, then the conditionally indicated upper level of the partition ℜ ₁ is a sequence of characters with odd numbers S _i ^н , while the lower level of the partition ℜ ₂ includes a sequence of characters S _i with even serial numbers S _i ^h :

отображаемый первой последовательностью троичных символов <S₂ S₂ S₁ S₀ S₁ S₀ S₀ S₀ S₁ S₁ S₂>₃, используют для первичной амплитудно-импульсной модуляции (АИМ), а поставленную в однозначное соответствие первой вторую последовательность троичных символов <T₂ T₂ T₁ T₀ T₁ T₀ T₀ T₀ T₁ T₁ T₂>₃ - для первичной широтно-импульсной модуляции (ШИМ) сформированного для передачи группового видеосигнала. В результате этого обеспечивают одновременную двумерную (АИМ и ШИМ) первичную модуляцию сформированного для передачи группового видеосигнала. При этом в (4) исходные N₁=17 символов двоичного кода будут заменены на N₂=11 символов троичного кода S_i и Т_i (i=0, 1, 2). Следовательно, скорость поступления символов в канал передачи информации уменьшится в полтора раза (k=N₁/N₂=17/11=1,54).The result of combining the upper and lower levels of the partition $${\Re }_{\mathrm{one}}\cup {\mathrm{<figure-callout\; id="2"\; label="R"\; filenames="00000018.png,00000019.png"\; state="\{\{state\}\}">\Re </figure-callout>}}_2,$$

displayed by the first sequence of ternary symbols <S ₂ S ₂ S ₁ S ₀ S ₁ S ₀ S ₀ S ₀ S ₁ S ₁ S ₂ > ₃ , used for primary amplitude-pulse modulation (AIM), and the second sequence unambiguously corresponds to the first ternary symbols <T ₂ T ₂ T ₁ T ₀ T ₁ T ₀ T ₀ T ₀ T ₁ T ₁ T ₂ > ₃ - for the primary pulse width modulation (PWM) generated for the transmission of a group video signal. As a result of this, simultaneous two-dimensional (AIM and PWM) primary modulation of the group video signal formed for transmission is provided. Moreover, in (4), the original N ₁ = 17 characters of the binary code will be replaced by N ₂ = 11 characters of the ternary code S _i and T _i (i = 0, 1, 2). Therefore, the speed of arrival of symbols in the information transmission channel will decrease by one and a half times (k = N ₁ / N ₂ = 17/11 = 1.54).

For clarity, in sequence (4), binary code combinations corresponding to the ternary code symbols S _i and T _i (i = 0, 1, 2) of the lower level of partition ℜ ₂ are underlined. In this case, the repeated symbols of the binary code at the boundaries of adjacent decryptions of the upper and lower levels, which, when generating the restored binary group signal, are combined into one binary symbol, are shown in bold.

Ternary code signals S _i and T _{i (i} = 0, 1, 2) in the secondary modulation are converted into tribasic frequency modulation (FM ₃₎ presented frequencies «f _n = f ₂ -Δf _d», «f ₁ = f _n + Δf _d "and" f ₀ = f _n ", and binary phase modulation, in which a phase change of 180 ° is performed at time instants that coincide with the pulse boundaries with the PWM.

The proposed method of recovering the transmitted information is as follows. Suppose that as a result of demodulation, the following fragment of the sequence of ternary signals S _{i is} restored:

1. The first data recovery operation in the source binary code is to extract the signals S ₂ that can be unambiguously decrypted: S ₂ ↔ "101". As a result of this, in the received sequence (2), a sign of receiving the symbol S _{2 is formed} , which is distinguished:

2. Conversion into binary code of the entire sequence of received ternary characters begins with the fact that the result of unambiguous decoding of S ₂ characters is written in binary code:

3. Then, using the first of the received signs of receiving the symbol S ₂ , one proceeds to decipher the ternary symbol S ₁ following it, to which not one, but two code combinations composed of binary symbols are assigned: S ₁ ↔ “10” and “ 001 ". Since, according to the condition for generating the proposed ternary code, the last binary character of the previous decryption 101 should be the first character of the subsequent decryption of the ternary symbol (in the given signal reception S ₁ ), then, as a candidate for replacement, choose code combination 10. Select the appropriate next code combination corresponding to the received signal S ₁ is determined by the last binary character obtained by decrypting the previous signal of the ternary code S ₂ (matching characters are shown in bold).

Further, the next restored ternary symbol corresponds to the signal S ₀ , which also has two possible decryption options: S ₀ ↔ "00" and "11". Since the previous decoding 10 ended with the binary character “0”, the next signal S ₀ must be replaced by a binary code combination consisting of two characters “0” - 00. Similarly, the next restored ternary character S ₁ ↔ “10” and “001” must be replaced by binary code 001. Then two characters S ₀ ↔ “00” and “11” follow in a row and, since the decoding of the previous binary code combination ended with the character “1”, the two subsequent ternary characters S ₀ must be replaced by a sequence consisting of the two characters “1” - 11. The fact that the decryption was done correctly is evidenced by the fact that the next ternary character will again be S ₂ ↔ “101”, which begins with the same binary character “1”, which was received at the end of the previous decoding signal S _0. The subsequent process of recovering transmitted messages in traditional binary code is similar. The correcting ability of the proposed code lies in the fact that the entire chain of ternary symbols recovered during reception is determined by the reference signals S ₂ ↔ "101".

4. The next operation assumes that the adopted sequence of ternary symbols S ₁ and S ₀ , allowing ambiguous decryption

replaced by a binary code so that the last binary decryption symbol of the previous symbol S _i , where i = 0, 1, 2, coincides with the first decryption symbol of the subsequent symbol S ₁ or S ₀ .

As a result of this, for sequence (8), the following reconstructed source binary code sequence is obtained:

where the "dots" are divided among themselves the results of decoding the symbols S ₁ and S _{0 of the} ternary code.

Then, the matching binary symbols at the boundaries of the decoding of ternary signals S _i , where i = 0, 1, 2, are combined and replaced with one corresponding binary symbol:

where matching characters are highlighted and underlined, which combine and replace with a single binary character.

As a result, the following fragment of the original binary code sequence will be restored: 10100011101.

The sequence of generated ternary symbols S _i , where i = 0, 1, 2, from the primary AIM and ternary symbols T _i , where i = 0, 1, 2, from the primary PWM are combined into a single pulse sequence of video signals (Fig. 1 (5) ) During their subsequent secondary modulation of the type: AIM ₃ -AM ₃ and AIM _3- FM ₃ , as well as PWM _3- FM ₂ ^{(3), the} modeled signal transmitted to the communication channel will have the form, a conditional illustration of which is shown in (Fig. 1 (6)). Moreover, from the comparison of the diagrams (Fig. 1 (1-8)), the following logical rule for combining various types of considered modulations follows: moments of phase change by 180 ° of the directly received signal U (t) with OFM (Fig. 1 (2)) and the signal U _com (t) with the proposed complex modulation (AM ₃ + FM ₃₊ FM ₂ ⁽³⁾⁾ (FIG. 1 (6)) coincide at time instants Incoming clock pulses (S _TI (t)), representing signal symbol timing source binary code (Fig. 1 (7)). Coincidences of this type establish the time instants of the beginning of binary symbols “1” of the source binary code. In this case, the moments of time that determine the end of the binary symbols “1” of the initial binary code correspond to the moments of phase changes by 180 ° for the delayed copy of the signal U _ass (t) with OFM (Fig. 1 (3)), since the delay time is equal to the duration ( T ₀ ) one character of the source binary code. The sequence A thus restored _in (t) of the symbols “1” of the binary code (FIG. 1 (8)) coincides with the symbols A _i (i = 0,1) of the original binary code (FIG. 1 (1)) and with the summation results directly received signal U (t) with OFM and its delayed copy of U _ass (t) (Fig. 1 (4)).

For clarity, the relationship of various modulation coding methods of transmitted information with more detail is presented in FIG. 2.

The established relationship creates the basis of logical rules that determine the possibility of sharing different types of secondary modulation of the transmitted group signal. This ensures the continuity of existing and developing information transmission systems using various problem-oriented coding and modulation methods.

The novelty of the invention also lies in the features that appear when identifying symbols of the transmitted code, distorted by noise during signal propagation (Fig. 3). From the above illustration, it follows that when transmitting information in binary code and using the proposed tri-basic coding, significant differences appear in the procedures for recognition (identification) of code symbols distorted by interference. When transmitting with binary code A _i (i = 0,1), there are no forbidden interpretations when presenting a group signal, since the binary character “0” can change both the character “1” and the newly repeated character “0” (Fig. 3 (a )). In this case, only the case of “hard” decoding (solution) is possible. When transcoding a binary code with the symbols {0,1} into the proposed logical tribasic code with the symbols {S ₀ , S ₁ , S ₂ }, forbidden sequences of characters appear in the group signal, for example, the sequence S ₂ S ₁ S ₂ (Fig. 3 (in )). Because of this, for example, the original code combination of characters: <101101> ₂ when transcoding on the transmitting side will be represented by the following sequence of characters: <S ₂ S ₀ S ₂ > ₃ (Fig. 3 (b)). But when received due to distortion, it will be “hard” decoding, suppose it is perceived as a sequence <S ₂ S ₁ S ₂ > ₃ , and it belongs to the number of forbidden ones (Fig. 3 (c)). As a result, it becomes possible to implement the soft decoding procedure (Fig. 3 (c)).

A block diagram of a device for implementing the method of transmitting information according to claim 1, including both transmitting and receiving sides, is shown in FIG. 4. In relation to the on-board radio telemetry system (BRTS), the transmitting side contains: sensors - 1 ₁ , 1 ₂ , ..., 1 _N , the outputs of each of which are connected to the corresponding N inputs of the signal compression and synchronization unit 2, the output of which is connected to the input of the transmitter 3 The signal compression and synchronization block 2 comprises a switch 4, the N inputs of which are the inputs of block 2, a logical ternary code generator 5, and a clock generator 6. The output 7 of the switch 4 is the input of the logical ternary code generator 5, the first output 8 of which is the output of the unit 2, and its second output 9 is connected to the input of the generator 6 of the clock signals, the output of which is connected to the (N + 1) input of the switch 4. The output of the transmitter 3 through a communication channel 10, subject to interference 11, is connected to the input of the receiver 12.

The receiving side contains a receiver 12 having four outputs - one service output 25 connected to the input of the selector 13 of the synchronization signals, and three information outputs connected to the first inputs 28, 29, 30 of the demodulators 16, 15 and 14 of the information signals, respectively, the second inputs of which combined and connected to the first output 26 of the selector 13 synchronization signals, the second output 27 of which is connected to the combined second inputs of the corrector 17, 19 and 22 of transmission errors, the first inputs of which through their corresponding decryptors 18, 20 and 21 of the red symbols are connected to the outputs of the corresponding demodulators 14, 15 and 16 of the information signals, the outputs of the corrector 22, 19 and 17 of transmission errors are connected respectively to the first 31, second 32 and third 33 inputs of the shaper 23 of the total message flow, the output of which is connected to the input of the decommutator 24, N outputs of which 34 ₁ , 34 ₂ , ..., 34 _N are the outputs of the device.

The block diagram of the logical ternary code generator 5 is no different from the prototype.

As a result of the proposed transformations, the binary code of the group signal generated by the switch 4, composed of a sequence of binary symbols “0” and “1”, is converted into a ternary code represented by the symbols “S ₀ ”, “S ₁ ” and “S ₂ ”, which are associated with pulse-amplitude modulation (AIM), and the symbols "T ₀ ", "1,5T ₀ " and "2T ₀ ", representing pulse-width modulation (PWM).

The device operates as follows. At the outputs of the sensors 1 ₁ , 1 ₂ , ..., 1 _N (Fig. 4), discrete values of the controlled telemetry parameters (TMP) are generated, which enter the signal compression and synchronization unit 2, in which the binary code consisting of the characters “0 "And" 1 ", in ternary code, represented by the symbols" S ₀ "," S ₁ "," S ₂ "with primary amplitude-pulse modulation (AIM) of their values and simultaneously with the symbols" T ₀ "," 1,5T ₀ ”And“ 2T ₀ ”when using primary pulse width modulation (PWM). In addition, the signs of the ternary symbols "S ₂ " and "2T ₀ ", which form the output 9 of the shaper 5 of the logical ternary code, are counted in the shaper 6 of the clock signals. The counting results are encoded using a binary code and transmitted along with the clock signal to the switch 4, which inserts them at the beginning of the next telemetric frame.

In the transmitter 3, triple modulation of the carrier signal to be transmitted via the communication channel 10 is performed, as a result of which, for example, the primary amplitude-pulse modulation (AIM) of the video signal is simultaneously converted to the secondary frequency modulation of the carrier signal and the corresponding amplitude modulation of the frequency-modulated (FM) signal, pulse width modulation (PWM) of the video signal is converted to phase modulation (FM) of the carrier signal. Thus, three-stage modulation is implemented in the form of: AIM _3- FM ₃ , AIM ₃ -AM ₃ and PWM _3- FM ₂ ⁽³⁾ .

To reduce out-of-band emissions when using the present invention, the first derivative is provided with continuity of the first derivative of the frequency-modulated signals generated for transmission at the boundaries of the symbols “S ₀ ”, “S ₁ ”, “S ₂ ”. This can be achieved by transferring the moment of transition from one radio symbol “S ₀ ”, “S ₁ ”, “S ₂ ” to another (opposite to it) not in the middle of the sine wave of the radio wave, but at its top, when their derivatives obtained from the previous the signal of one frequency and the signal of another frequency, replacing it, are equal.

As a result of applying the method, the following three-stage modulation scheme is implemented:

The transition from a binary digital baseband farm signal <x> ₂ to the three-stage modulation of these two types: PAM ₃ → FM _3, PAM ₃ → AM ₃ and PWM ₃ → FM ₂ ⁽³⁾ leads to the fact that each transmitted ternary symbol S _i able to carry 1.6 times more information than binary code. This conclusion follows from the relation log ₂ 3 = 1.6.

A three-dimensional base modulation three-way code modulation method, which is illustrated in FIG. 1, provides the ability to combine different modulation methods implemented on the basis of the same carrier frequency of the signal. In this case, the tribasic AIM signals represented by the ternary code symbols “S ₀ ”, “S ₁ ” and “S ₂ ” are converted, for example, into the frequencies “частоты ₂ = ƒ _n -Δƒ _d ”, “» ₁ = ƒ _n + Δƒ _d ”and“ ƒ ₀ = ƒ _n ”, respectively, where ƒ _n is the value of the carrier frequency of the signal, and Δƒ _d is the value of the frequency deviation. Thus, each of the ternary symbols corresponds to its own frequency value ƒ ₂ , ƒ ₁ , ƒ ₀ (Fig. 1). In addition, at the boundaries of the tribasic coding intervals corresponding to the ternary code symbols "T ₀ ", "1.5T ₀ " and "2T ₀ ", the frequencies ƒ ₂ , ƒ ₁ and ƒ _{0 are} modulated in accordance with the primary PWM ₃ phase modulation. As a result, two phase changes by 180 ° are obtained, which coincide with the PWM ₃ pulses. The resulting modulation is denoted as FM ₂ ⁽³⁾ .

Consequently, the boundary intervals tribasic coding emit three times: first frequency detector due occurring frequency change, the second time amplitude detector, since the amplitude of the respective frequency ƒ _2, ƒ ₁ and ƒ ₀ take the values: A _0, A ₁ and A _2, and a third time with a phase detector, which establishes the fact that the phase of the modulated frequency changes by 180 °.

This contributes to the further development of the method [4], since, in addition to frequency and phase modulation, amplitude modulation of the carrier signal is also used. Moreover, amplitude detection does not have fundamental differences from the existing practice of amplitude demodulation. For the frequency detection of the transmitted signal at the receiving side, three parallel detection channels are used, in each of which signal fragments corresponding to frequencies ƒ ₂ , ƒ ₁ and ƒ ₀ are allocated with a narrow-band filter installed at the input, in each of which local oscillators are tuned to the input signal in frequency and amplitude, fill in the time intervals corresponding to the transmission of other frequencies.

Three copies of the group signal reconstructed in this way, corresponding to frequencies ƒ ₂ , ƒ ₁ , ƒ ₀ and amplitudes A ₀ , A ₁ , A ₂ , are subjected to simultaneous phase demodulation in each of the three channels.

Thus, a technical result is achieved, consisting in the following:

- in the compression of signals in the communication channel and the extension on this basis of its bandwidth;

- in ensuring control and correction of errors caused by interference of various origins;

- to increase the secrecy of data transmission due to the simultaneously used various methods of message conversion - the existing binary representation of sync words and the proposed ternary encoding of the transmitted content information.

The present invention can be used to increase the energy potential of the “Bort-Earth” radio line when transmitting telemetric information (TMI) from ballistic missiles (BR), launch vehicles (LV), booster blocks (RB) and spacecraft (SC) in the conditions of their tests and regular operation (ШЭ). It forms the basis for the construction of a new adaptive information and telemetry support (SITO) system for testing BR and SHE rocket and space technology (RKT), the effectiveness of which is enhanced by using more efficient noise-resistant coding compared to the known analogues. It is based on the transition from the traditional binary code to the ternary logical coding proposed in the present invention.

When applying the present invention, an increase in the equivalent energy of transmitted bits of information by 3-6 dB will be ensured. At the same time, the requirements for reducing the information transfer rate and at least 1.33 times the requirements for the bandwidth of the communication channel will be reduced by no less than 1.5 times, which is especially important in conditions of rapidly growing streams of transmitted messages.

As a result of the use of the present invention, it will be possible to detect and correct errors without introducing redundancy in the transmitted characters due to the special design of the proposed logical three-base codes. In this case, the three-basic code will be substitute and will be used only when transmitting information. For analysis and processing, it can again be converted to traditional binary code. In addition, the number of code combinations “101” calculated on the transmitting side in the shaper 6 for a period equal to the duration of the telemetric frame is compared with the received and reconstructed number of these combinations in the same telemetric frame on the receiving side, and their difference is used to evaluate the quality of the communication channel , as well as indicators of the integrity and reliability of the received information.

The technical result, which assumes in the new method the comparability of the results of demodulation of traditional relative phase modulation (OFM) with base two, used for transmission over the main communication channel, and the proposed ternary phase modulation with base two (FM ₂ ⁽³⁾ ), which are based on logical noise-proof codes with three base represented by the symbols (S ₀ and T _0, S ₁ and T _1, S ₂ and T _2), and which is used to transmit information on both the main and by duplicating the radio channel, the phase change per the signal given by 180 ° at the time points defining the boundary of the generated pulse widths of tribasic code "T _0», «1,5T _0» and «2T _0", where T ₀ - duration of "0" or a binary symbol "1" of the primary binary , ensure that on the receiving side, the integrity and reliability of the information transfer is controlled based on the coincidence of the time points of the phase change of the transmitted signal by 180 ° in both communication channels and the time of appearance of the clock (symbol) synchronization signals that coincide with the boundaries of the change of two different symbols of the initial group signal, while the coincidence moments determine the beginning of the binary code symbol “1” restored when the initial group signal is received, and based on all other moments of the phase change that did not coincide in time in the main and duplicate information transmission channels, they are used to determine signs of the formation of characters of the binary code "0" restored when receiving the initial group signal, the beginning of which coincides with the moments of receipt of the corresponding clock signal (symbol noy) synchronization possible transmission errors occurring under the action of interference, correct due to the redundancy logic error-correcting code with the base three (T _{i i} = 0, 1, 2), which symbol boundary is determined based on phase modulation involves changing the phase by 180 ° at the time points corresponding to the boundaries of the ternary symbols (T _i , i = 0, 1, 2).

A device for implementing the method (Fig. 4), comprising a transmitter and sensors on the transmitting side, the outputs of which are connected to the corresponding inputs of the signal compression and synchronization unit, which includes a switch, a logic ternary code generator, and a clock generator, while N switch inputs are inputs block of signal compression and synchronization, and the output of the switch is connected to the input of the shaper of the logical ternary code, one of the outputs of which is the output of the block of compression and synchronization signal conditioning, and the second output is connected to the input of the clock generator, the output of which is connected to the (N + 1) -th input of the switch, the output of the transmitter through the communication channel is connected to the input of the receiver having four outputs - one service output connected to the input of the synchronization signal selector , and three information connected to the inputs of the first, second and third demodulators of information signals, respectively, the second inputs of which are combined and connected to the first output of the selector of synchronization signals, the second output it is connected to the combined second inputs of the first, second, and third transmit error correctors, the first inputs of which are connected to the outputs of the corresponding first, second, and third demodulators of information signals through the first, second, and third decryptors of the information signals, and the outputs of the first, second, and third transmit error correctors connected to the corresponding inputs of the generator of the general message flow, the output of which is connected to the input of the decommutator, N outputs of which are outputs of troystva.

The present invention differs from prototypes and analogues in the following essential characteristics:

a) it creates fundamentally new conditions for increasing the efficiency of information transmission systems based on the transition from traditional positional binary coding to a more economical ternary code;

b) it creates the basis for enhancing the claimed technical effect when combining various types of error-correcting coding.

When using the proposed method, a technical result also appears, allowing without significant modifications to present the analog signals of analog and combined telemetry systems (Fig. 5) [5] at the output of the transmitting devices as digital.

Moreover, only due to the combined modulation of the carrier signal, analog values corresponding to the values of 0%, 50% and 100% of the scale of their presentation (Fig. 5) ([5], "Modern telemetry in theory and practice / Training course", St. Petersburg. : Science and Technology, 2007. - 672 p., P. 248), form as data represented by a digital code with a base of three, followed by their formal replacement by ternary code symbols "S ₀ " and "T ₀ ", "S ₁ "And" T ₁ "," S ₂ "and" T ₂ ".

The practical significance of such a replacement is significant, since analog telemetry systems are still the most popular in domestic practice when providing measurements of rapidly changing parameters (BMP).

As a result of the proposed replacement, for example, the corresponding analog signals in the combined Sirius BRTS (Fig. 5) ([5], p. 244-250) will be perceived as digital when receiving, corresponding to the following binary combinations when decrypted: 1) analog value 0% of the presentation scale should be interpreted as code combinations (00 or 11) of the binary code: (0% ↔ (“S ₀ ” and “T ₀ ”) ↔ (00, 11)), 2) the analog value of 50% of the presentation scale will correspond (↔) a unique binary code combination (101): (50% ↔ (“S ₂ ” and “T ₂ ”) ↔ (101)), 3) analog value 100% of the presentation scale will be perceived as code combinations (10, 001) (100% ↔ (“S ₁ ” and “T ₁ ”) ↔ (10, 001)).

As a result of such a formal replacement in the Sirius BRTS, the clock signal of the main switch-former (OKF), called the “marker level” (39 and 40 channels, as well as the active pause between them), and the corresponding 50% of the analogue representation scale will be identified upon reception with symbols of the ternary code S ₂ S ₂ S ₂ , which corresponds to the following excessive decoding of the binary code: 101101101 or 1010101 when it is compressed. Since the Sirius BRTS uses AIM-FM type modulation: AIM _2- FM ₂ , AIM _4- FM ₄ to transmit information about slowly varying parameters (MMP), as well as AIM-FM for BMP transmission, then use the proposed ternary code "S ₀ "," S ₁ "and" S ₂ "will allow you to replace AIM ₂ -FM ₂ , AIM ₄ -FM ₄ with AIM ₃ -FM ₃ using three fixed frequency values of the transmitted signal" f ₂ = f _n -Δf _d ", "F ₁ = f _n + Δf _d " and "f ₀ = f _n ", where f _n is the value of the carrier frequency of the signal, and Δf _d is the value of the frequency deviation equal to 800 KHz for the Sirius BITS. In the case of using a 4-position code, FM ₄ is represented by the following correspondences: 1) code combination “00” ↔ 0% ↔ f ₂ = f _n -Δf _d ; 2) codeword "01» ↔33% ↔f ₃ = f -Δf _{d n} / 4; 3) the code combination "10" ↔67% ↔f = f _n + Δf _d / 4; 4) the code combination "11" ↔100% ↔f ₁ = f _n + Δf _d . Also, when transmitting the analog signal “on-board calibration (BC)” (channel 30), which is a sinusoidal oscillation of 1000 Hz, interrogated with a frequency F _op = 8000 Hz, the measured values also have the form of a 4-position code (Fig. 5). Therefore, there are also no fundamental difficulties in translating the analog signal of the BC (channel 30) into the proposed 3-position code. In this case, the existing 2-position and 4-position coding structure (Fig. 5) will be replaced by the proposed 3-position code “S ₀ , T ₀ ”, “S ₁ , T ₁ ”, “S ₂ , T ₂ ” with simultaneous AM modulation ₃ + FM ₃ + FM ₂ ⁽³⁾ .

Thus, the technical effect will be manifested in the possibility of the easiest transition in existing analogue BRTS to digital methods of information transfer.

Claims (5)

1. A method of transmitting information, which consists in collecting signals from message sources, synchronizing them in time, generating a compressed signal from synchronized collected signals, generating a carrier frequency signal, modulating the carrier frequency signal with a compressed group signal based on the generated video code, transmitting the modulated signal over the communication channel the binary video signal of service and information messages formed for transmitting information is converted into a substitute ternary after its compaction nth error-correcting code, which is formed on the basis of the adopted logical coding rule, and on the basis of the adopted logical coding rule at the first stage of binary code transformations, two components of the modulating video signal are designed to modulate the carrier frequency of the transmitted signal, each of which has three coding symbols, conditionally defined as «S _0» and «T _0», «S _1" and «T _1», «S _2" and «T _2", the first modulating component tribasic converted first video signal containing B oxen «S _0», «S _1" and «S ₂ 'are in the form of pulse amplitude modulation, and the second modulating component of the video signal with symbols tribasic code« T ₀ »,« T ₁ "and« T ₂ "where T ₀ - the duration of one symbol original binary code is used for pulse width modulation of the second video signal, wherein the second phase transformation associated with the transmitted modulated carrier signal pulse amplitude modulation generated by the video signal is converted, for example, a frequency modulation signal are fixed with three and the values of frequency of the transmitted signal «f _n = f ₂ -Δf _d», «f _n = f ₁ + Δf _d" and «f ₀ = f _n" where f _n - value of the carrier signal frequency, Δf _d - the frequency deviation and the second component of the generated video signal is used to phase modulate the transmitted signal by changing the phase by 180 ° at the boundaries of time intervals corresponding to the ternary symbols “T ₀ ”, “T ₁ ” and “T ₂ ”, characterized in that on the transmitting side, on a second step «f _n = f ₂ -Δf _d», «f _n = f ₁ + Δf _d" and «f ₀ = f _n" of the amplitude transformation the transmitted signal frequency also resulting in in accordance with the values of a pulse amplitude modulation symbols transmitted ternary code «S _0», «S _1" and «S _2" formed on the first stage transformations, whereby characters ternary «S _0" code, «S _1" and " S ₂ "in the secondary modulation of the signal is repeated twice: once by changing the frequency of the signal, taking the values of" f ₂ = f _n -Δf _d "," f ₁ = f _n + Δf _d "and" f ₀ = f _n ", and second time - corresponding change of its amplitudes A _0, A _1, A _2, wherein on the receiving side to demodulate the generated signal on the transmission side, in addition to portions deleterious demodulator constructed in quality narrowband filter tuned to the frequency «f _n = f ₂ -Δf _d», «f _n = f ₁ + Δf _d" and «f ₀ = f _n" and phase demodulators each channel allocation the frequency components of the received signal, an amplitude demodulator is used as an independent channel for demodulating the received signal, restoring the values of the amplitudes A ₀ , A ₁ , A ₂ , the obtained results of the amplitude demodulation A ₀ , A ₁ , A ₂ , which are unambiguously corresponded to the symbols of the proposed ternary code " S ₀ "," S ₁ "and" S ₂ "are compared with data obtained by the frequency and phase demodulators, the comparison results are used to increase the reliability of receiving telemetric information. 2. A method according to claim 1, consisting in that for demodulation on the receiving side of the new combination of modulation type, which is a simultaneous change of frequency and amplitude in accordance with tribasic code formed the sequence transmitted over the communication channel frequency «f ₂ = f _n. - Δf _d ”,“ f ₁ = f _n + Δf _d ”and“ f ₀ = f _n ”of the signal, which unambiguously correspond to the symbols of the three-basic code of the first type:“ S ₀ ”,“ S ₁ ”and“ S ₂ ”, the generated signal with frequency modulation into three fixed frequency values, additionally m duliruyut using a phase modulation signal formed by changing the phase by 180 °, which is produced with respect to the frequency «f _n = f ₂ -Δf _d», «f _n = f ₁ + Δf _d" and «f ₀ = f _n ' at times coinciding with the boundaries of ternary symbols of the second type: “T ₀ ”, “T ₁ ” and “T ₂ ” having primary pulse-width modulation with duration values T ₀ , T ₁ = 1,5T ₀ , T ₂ = 2T ₀ , respectively, while the amplitudes of the sinusoids A ₀ , A ₁ , A _{2 of the} transmitted frequency-modulated signal with frequency values "f ₂ = f _n -Δf _d ", "f ₁ = f _n + Δf _d " and "f ₀ = f _n "put in unambiguous with correspondence with the values of the amplitudes of the symbols of the tribasic code of the first type: "S ₀ ", "S ₁ " and "S ₂ ", obtained with their primary amplitude-pulse modulation, characterized in that when receiving information at the same time three carrier signals are extracted with three narrow-band filters, corresponding to the frequencies “f ₂ = f _n -Δf _d ”, “f ₁ = f _n + Δf _d ” and “f ₀ = f _n ”, with the simultaneous formation of three parallel demodulation channels, in each of which the selected frequency is phase modulated by group a signal formed on the transmitting side in each demodulation of parallel channels are formed by local oscillators priori known frequency «f _n = f ₂ -Δf _d», «f _n = f ₁ + Δf _d" and «f ₀ = f _n" with predetermined amplitudes A _0, A ₁ and A ₂ , unambiguously corresponded with the ternary code symbols "S ₀ ", "S ₁ " and "S ₂ ", while local generators adjust the frequency components "f ₂ = f _n -Δf _d ", "f ₁ = f to the received signals _n + Δf _d »and« f _n = f ₀ ", based on the respective signals generated by the mismatch between the frequencies of the received signal and the frequencies of the local oscillators fill interruptions associated with the transmission of other frequencies at this time “f ₂ = f _n -Δf _d ”, “f ₁ = f _n + Δf _d ” and “f ₀ = f _n ”, by adding carrier frequencies of local oscillators of the corresponding frequency and amplitude up to the formation of time-continuous information transfer frequencies “f ₂ = f _n -Δf _d ”, “f ₁ = f _n + Δf _d ” and “f ₀ = f _n ” with preservation of the moments of phase change by 180 °, subject them to simultaneous phase demodulation as a result of which, for each of the three parallel demodulation channels, the results of frequency and phase demodulation are supplemented, each of which x is presented in the form of direct and inverse copies of video signals with binary coding logic adopted for transmitting information; the integrity and reliability of transmitted messages restored by frequency and phase demodulation of the received signal are checked based on pairwise addition of the generated direct and inverse copies of video signals represented by logical levels of binary code adopted for transmitting information, the result is compared with the results obtained with amplitude detection of prin signal. 3. The method according to p. 1, which consists in the fact that on the transmitting side of the binary code form video signals with a base of two (A _i , i = 0,1), and with a base of three (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ), for the transfer of which parallel communication channels are used, while the traditional radio channel with relative phase modulation (OFM) of the video signal of the original binary group symbol sequence (A _i , i = 0, 1), and in an additional communication channel that uses logical noise immunity to transmit duplicate information active codes with a base of three (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ), a sequence consisting of formed ternary characters (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ) modulated signal transmitted by duplicating the communication channel using several kinds of different secondary modulation, for example amplitude with base three, frequency-base three and phase with a base of two (FM ₂ ^(3)), the binary combinations ( "00" and "11") of the initial sequence of binary symbols correspond to the ternary code symbols "S ₀ and T ₀ ", code combinations of the source binary code group signal (“001” and “10”) are replaced by ternary code symbols “S ₁ and T ₁ ”, and the ternary code symbols “S ₂ and T ₂ ”, on the receiving side, when decoding ternary symbols, conventionally designated as (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ), the uniqueness of the restoration of transmitted messages is checked during the reverse translation of the ternary code to the source binary code based on checking the conditions for the coincidence of the last two character “0” or “1” of the previous decryption of the received ternary symbol with the first character “0” or “1” of the subsequent decryption, while there is an error in receiving ternary characters (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ) are determined both on the basis of violation of this rule and by matching the phase values changing by 180 ° for signals modulated using relative phase modulation (OFM) of the original group signal sequence represented by the traditional binary code and phase modulation with a base of two ₍₂ FM ^(3)), koto Separated was used in the transmission baseband signal, represented by a logical error-correcting code symbols with base three (T _0, T ₁ and T ₂₎ with the primary pulse-width modulation, the integrity and authenticity of the received information is evaluated based on the synchronous alignment temporal coincidence data sequence 180 ° phase changes with OFM and the proposed binary phase modulation (FM ₂ ⁽³⁾ ) with the boundaries of the periodic sequence of binary code symbol synchronization signals, which It is a restored copy of the original results of encoding the television measurements received on the transmitting side when received, the absence of the listed coincidences is perceived as the fact of errors that appeared during the transmission and reception of information. 4. The method according to p. 1, which consists in ensuring that the results of demodulation of traditional relative phase modulation (OFM) are comparable with base two used for transmission over the main communication channel and the proposed ternary phase modulation with base two (FM ₂ ⁽³⁾ ), which is based on logical error-correcting codes with a base of three, represented by symbols (S ₀ and T ₀ , S ₁ and T ₁ , S ₂ and T ₂ ), and which is used to transmit information both on the main and duplicate radio channels, with phase change of the transmitted signal 180 ° at the time points defining the boundaries of the pulse duration of the generated tribasic code "T ₀ ", "1,5T ₀ " and "2T ₀ ", where T ₀ is the duration of the binary character "0" or "1" of the primary binary code, ensure that, on the receiving side, the integrity and reliability of the information transfer is controlled based on the coincidence of the time points of the phase change of the transmitted signal by 180 ° in both communication channels and the time of appearance of the clock (symbol) synchronization signals coinciding with the boundaries of the binary symbols the initial group signal, while the coincidence moments determine the beginning of the binary code symbol “1” restored when the initial group signal is received, and based on all other moments the phase changes that did not coincide in time in the main and duplicate information transmission channels are used to determine the signs of formation characters of the binary code "0" restored when receiving the initial group signal, the beginning of which coincides with the moments of receipt of the corresponding signal of the clock (symbol) synchronization ation, possible transmission errors occurring under the action of interference, correct due to the redundancy logic error-correcting code with the base three (T _{i, i} = 0, 1, 2), which symbol boundary is determined based on phase modulation involves changing the phase by 180 ° a ternary symbols corresponding to the boundaries (T _{i, i} = 0, 1, 2) times. 5. A device for implementing the method of transmitting information according to claim 1, comprising a transmitter and sensors on the transmitting side, the outputs of which are connected to the corresponding inputs of the signal compression and synchronization unit, including a switch, a logical ternary code generator, and a clock generator, with N inputs the switch are the inputs of the signal compression and synchronization unit, and the output of the switch is connected to the input of the logical ternary code generator, one of whose outputs is the output of the and the signal is sealed and synchronized, and the second output is connected to the input of the clock generator, the output of which is connected to the (N + 1) -th input of the switch, the output of the transmitter through the communication channel is connected to the input of the receiver having four outputs - one service output connected to the input selector synchronization signals, and three information connected to the inputs of the first, second and third demodulators of information signals, respectively, the second inputs of which are combined and connected to the first output of the selector signals nation, the second output of which is connected to the combined second inputs of the first, second and third transmit error correctors, the first inputs of which through the corresponding first, second and third ternary decryptors are connected to the outputs of the corresponding first, second and third demodulators of information signals, the outputs of the first, second and the third error corrector transmission are connected to the corresponding inputs of the shaper of the total message flow, the output of which is connected to the input of the decomposer, N outputs of which are the outputs of the device.

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