RU2475861C1 - Method of transmitting information and device for realising said method - Google Patents

Abstract

FIELD: physics.

SUBSTANCE: signals are generated at the transmitting side at first and second subcarrier frequencies f_H1 and f_H2, which differ from the carrier frequency by the frequency modulation depth value (deviation) Δf: f_H1=f_H+Δf and f_H2=f_H-Δf, and two different models are used to represent the binary code of the group signal with logic levels defined as "low" and "high" potential. The first model is the original model and comprises binary logic pulses with symbol duration τ_c, and the second is a derivative obtained from the first by addition with a square wave which represents clock pulses with duration

According to the law of variation of the first series of binary logic levels, each of the subcarrier frequencies is phase modulated with conversion of the sine curve to a cosine curve and vice versa. The second binary logic is used to perform time compression of two subcarriers, owing to which only one information transmission channel is used.

EFFECT: more secure and reliable unlocking of any secure technical objects having an actuating locking mechanism in their composition.

3 cl, 4 dwg

Description

The invention relates to telemetry, communication technology and can be used in data transmission systems over communication channels. Its use allows to increase the reliability of information transfer without introducing structural redundancy in transmitted messages based on the simultaneous use of two different types of modulation.

The closest analogue is the method of transmitting information (see Kukushkin S.S., Moroz A.P. Patent of the Russian Federation No. 2115172 "Method of transmitting information and a device for its implementation", priority of the invention from 03/10/1993, M. class. G08C 19/28, published July 10, 1998, Bulletin No. 19 ([1])), which consists in collecting signals from message sources, synchronizing them in time, generating a compressed signal from synchronized collected signals, generating a signal of the first carrier frequency, phase shift keying the signal of the first carrier frequency, the compressed signal, p transmitting the modulated signal through a communication channel, characterized in that they generate a second carrier frequency signal, generate a periodic sequence of a meander-type pulse signal with a pulse duration half the minimum pulse width of the compressed signal, phase-shift the second carrier signal with a compressed signal, and then form the modulated signal to be transmitted over the communication channel by frequency manipulation of the phase-shifted signals of the first and second non natural frequencies by a pulse signal of a phase-manipulated periodic sequence.

The invention [1] is aimed at increasing the efficiency of information transfer by compressing the signals transmitted in the communication channel, which consists in the simultaneous use of frequency and phase manipulation. Its main disadvantage is that the method of receiving the generated complex signal was not presented.

All modern information transfer technologies include noise-resistant coding of transmitted information. However, the traditionally prevailing idea of error-correcting coding is associated with error-correcting codes, in which the required redundancy is formed at the level of binary characters “0” and “1” (see Clark, J., Jr., Kane, J. Coding with error correction in digital communication systems. / Translated from English. - M.: Radio and Communications, 1987. - 392 p. ([2])). The modern concept of noise-resistant coding involves the use of distributed technology of noise-resistant coding, which, first of all, means a double (two-dimensional) representation of data and signals, as well as the use of different codes at the level of video signals and the simultaneous use of different types of modulation of the carrier frequency. In the latter case, the object of application of error-correcting coding is the level of presentation of the transmitted information by radio signals. At its core, this is a new stage of information coding, but carried out at the stage of signal modulation.

The invention is also known (see S. Kukushkin, V. I. Kolesnikov, “Device for Monitoring the Reliability of Telemetric Information”, ed. Certificate of the USSR No. 1596365 dated May 6, 1987, published September 30, 1990, bull. No. 36 [3]), in which it was first proposed to use the presentation of data by their residual images to transmit information in order to control the reliability of receiving a single value of a telemetry parameter (TMP). When applying the invention [3], previously indivisible transmitted messages, which are, for example, TMP values encoded by 2n-bit binary measurement words, are divided into two independent information elements having half the bit capacity. The technical effect obtained in this case can be characterized as the result of a new two-dimensional representation of the original message x with two or more residual images b ₁ and b ₂ obtained from dividing the number x by the selected comparison modules m ₁ and m ₂ in a certain way. In the case when there are more than one comparison module (i≥2), such a representation is called a system of residual classes (RNS) (see Torgashev V.A. System of residual classes and the reliability of a digital computer. - M .: Sov. Radio, 1973. - 120 p. [4]). Presentation of data in the RNS opens up fundamentally new opportunities for implementing highly efficient noise-resistant coding of transmitted information.

The basic invention [1] in accordance with the current classification relates to the field of noise-resistant compaction and transformation of transmitted information, the implementation of which is associated with the level of modulation of the signals. It also, in accordance with the theory of distributed error-correcting coding, the initial binary code must first be presented in two-dimensional form. In the invention [1], each such type is represented by its regularity, establishing an unambiguous correspondence between the source binary code and the logical levels of its presentation formed by video signals.

Combining several types of modulation allows using a single information transmission channel to create redundancy of transmitted binary code symbols at the signal level. For this, the digital group stream of binary code symbols originally formed in the traditional form at the level of video signals is divided into two such independent components, in which the changes in the logical levels corresponding to the symbols “0” and “1” do not coincide in time. The fulfillment of this requirement leads to the possibility of the simultaneous use of two different types of modulation of one carrier signal. In this case, one sequence of logical levels of the binary code generated during separation modulates the carrier of the signal in phase, and another sequence of logical levels of binary code modulates the carrier of the signal in frequency.

As a result of this, temporary compression of the generated copies of the signals in the transmitter is performed using only one carrier of the transmitted signal. In traditional practice, temporary compaction is used only at the level of TMP video signals and channel switches are used to accomplish this task (see. "Modern Telemetry in Theory and Practice / Training Course", St. Petersburg: Nauka i Tekhnika, 2007. - 672 p. [5 ], p. 248, 249).

The technical effect obtained in this way leads to signal compression in the communication channel. An analogue of this approach can also be considered the technology of syntactic compression of the transmitted data, however, it is traditionally focused on the previous stage of information transformation associated with the formation of video signals. The level of video signals is also considered as the first stage of pulse-code modulation (CMM _k ) of a digital group message stream, where k is the base of the code [5]. This level of modulation coding is traditionally represented by such modulations as pulse-amplitude modulation (AIM _k ), time-pulse (VIM _k ), or pulse-width (PWM _k ). The only difference between the latter and the AIM, VIM, or PWM modulations used in the transmission of analog information is in the presence of the code base index k, which indicates that not a continuous source signal is modulated, but the results of representing code values with base k (with a limited number k its predetermined positions). The transformations carried out in the proposed invention with respect to the carrier of the transmitted signal belong to the next second modulation level [5].

Due to the achieved technical effect, which consists in replicating copies of transmitted messages during modulation, they provide the ability to detect and correct errors that occur during the transmission of information.

The technical result is achieved by the fact that in the method of transmitting information, which consists in collecting signals from message sources, synchronizing them in time, generating a compressed signal from synchronized collected signals, generating a signal of the first carrier frequency, phase manipulating the signal of the first carrier frequency with a compressed signal, transmitting the modulated signal through the communication channel, form a signal of the second carrier frequency, form a periodic sequence of a pulse signal of the meander type with a duration of After a pulse, twice the minimum pulse width of the compressed signal, phase-shift keying of the second carrier signal is performed by the compressed signal, and then the modulated signal to be transmitted via the communication channel is generated by frequency-shift keying of the phase-manipulated signals of the first and second carrier frequencies by a pulse-phase-manipulated periodic signal, at receiving information, perform the following operations: simultaneously, the signals of the first and second carrier frequencies are isolated phase-modulated by a digital group signal, form copies of the first and second carrier frequencies by local generators, which are tuned to the received carrier signals based on the generated corresponding mismatch signals, fill in the gaps associated with the transmission of another carrier frequency at this time, by adding the carrier frequency signals of the local generators of the corresponding frequencies before the formation of time-continuous carriers of the first and second information transmission frequencies, subject them to simultaneous phase demodulation As a result, direct and inverse copies of video signals with binary coding logic adopted for transmitting information are generated, the integrity of the transmitted messages is checked based on the addition of the generated direct and inverse copies of video signals with logical levels of binary code adopted for transmitting information, which are simultaneously restored when receiving continuous in time carriers of the first and second frequencies of information transmission are subjected to frequency demodulation, as a result of which I also form a direct and inverse copy of video signals with binary coding logic, which was used before modulating the signals in the transmitting device, control the integrity and reliability of the transmitted messages based on the addition of direct and inverse copies of video signals with binary coding logic used to transmit information that was used before the modulation of signals in the transmitting device, based on the received four signal copies of the transmitted information and the formed signs of integrity and reliability control and transmitted messages correct transmission errors and form in binary code a single stream of transmitted information with corrected errors.

каждый в прямом (эпюра в)) и инверсном (эпюра г)) виде. На эпюре д) и эпюре е) изображены первая и вторая несущие частоты, а на эпюре ж) представлены результаты суммирования исходной последовательности уровней двоичной логики (эпюра а)) и синхронизирующего меандра (эпюра в)). Эпюра, представленная как эпюра з), представляет собой сумму инверсной последовательности уровней двоичной логики (эпюра б)) и инверсного синхронизирующего меандра (эпюра г)). Далее сигналы, представленные на эпюрах ж) и з), также суммируются с образованием второй последовательности уровней двоичной логики (эпюра и)). Эпюра к) представляет собой инверсную последовательность по отношению к ранее полученной последовательности, представленной на эпюре и). Затем первую несущую частоту модулируют по фазе первой последовательностью, представленной на эпюре а), в результате чего получают эпюру н). Аналогичную операцию проводят и по отношению ко второй несущей частоте. Далее используют вторую последовательность уровней двоичной логики (эпюра и)) для временного уплотнения (коммутации) первой и второй несущих, промодулированных по фазе по следующему правилу: во время действия высокого логического уровня последовательности (эпюра и)) передаче подлежит промодулированная по фазе первая несущая частота, при низком логическом уровне в эфир излучают промодулированную по фазе вторую несущую частоту. В результате этого формируют уплотненный сигнал, приведенный на эпюре т), в котором одновременно используют как фазовую, так и частотную модуляцию. При этом частотную модуляцию, формируемую в результате объединения двух несущих частот, о чем шла речь в прототипе [1], рассматривают как результат частотной модуляции одной несущей частоты f₀, осуществляемой по правилу: f₁=f₀-Δf_д, a f₂=f₀+Δf_д, где f₀ - воображаемая одна несущая частота, Δf_д - индекс модуляции (девиация) несущей частоты f₀.The transmitting device remains the same as that of the prototype [1]. The diagrams presented in figure 1, explain the essence of the invention and the sequence of operations of signal transformations performed on the transmitting side. They have additional letters from a) to t). Similar designations are adopted in the invention [1]. For example, diagram a) illustrates the initial simple rule for representing a sequence of binary symbols of a group telemetric signal (GTS): 10110011010 by binary logic levels with a duration of one symbol equal to τ _c . Diagram b) shows the inverse (inverse) with respect to diagram a) a sequence of levels of binary logic. Below are presented in the form of a meander sequence of synchronizing pulses of duration

each in direct form (diagram c)) and inverse (diagram d)). Diagram e) and diagram e) show the first and second carrier frequencies, and diagram e) shows the results of summing the initial sequence of binary logic levels (diagram a)) and a synchronizing meander (diagram c)). The diagram presented as diagram h) is the sum of the inverse sequence of binary logic levels (diagram b)) and the inverse synchronizing meander (diagram d)). Further, the signals presented on the diagrams g) and h) are also summed up with the formation of a second sequence of levels of binary logic (diagram i)). Diagram k) is an inverse sequence with respect to the previously obtained sequence shown in diagram i). Then, the first carrier frequency is phase-modulated by the first sequence shown in plot a), resulting in a plot of n). A similar operation is carried out with respect to the second carrier frequency. Next, use the second sequence of binary logic levels (plot and)) for temporary compaction (switching) of the first and second carriers, phase-modulated according to the following rule: during the action of a high logical level of the sequence (chart and)), the phase-modulated first carrier frequency must be transmitted , at a low logical level, the second carrier frequency modulated in phase is emitted into the ether. As a result of this, a compressed signal is generated, shown in plot t), in which both phase and frequency modulation are simultaneously used. In this case, the frequency modulation generated by combining the two carrier frequencies, which was discussed in the prototype [1], is considered as the result of the frequency modulation of one carrier frequency f ₀ carried out according to the rule: f ₁ = f ₀ -Δf _d , af ₂ = f ₀ + Δf _d , where f ₀ is the imaginary single carrier frequency, Δf _d is the modulation index (deviation) of the carrier frequency f ₀ .

On the receiving side, the transmitted compressed signal, modulated in frequency and phase, must be subjected to the reverse operation - decompression, the purpose of which is to restore one of the carrier frequencies in those time intervals when the other carrier frequency was subject to transmission. If this is not done, then the demodulation of the transmitted signal in frequency and phase cannot be performed with high reliability. The proposed method is dedicated to solving this problem.

Figure 2 shows the structural diagram of a device that receives and demodulates information transmitted using a double logical sequence of binary code levels and double modulation of the carrier of the transmitted signal.

Figure 3 and 4 shows diagrams explaining the method and operation of the receiving device. At the same time, FIG. 3 presents diagrams characterizing the method and operation of the receiving device under conditions when there are no transmission errors, and FIG. 4 presents the same diagrams for the case when there are errors.

The device (figure 2) contains a receiver 1, adders 8 ₁ and 8 ₂ , a generator 9 of a generalized bit stream of transmitted information, the output of which 22 is the output of the device, as well as two blocks 10 ₁ and 10 _{2 of} signal demodulation, including bandpass filters 2 ₁ and 2 ₂ , clocks 3 ₁ and 3 ₂ , generators 4 ₁ and 4 ₂ frequencies, switches 5 ₁ and 5 ₂ signals, phase demodulators 6 ₁ and 6 ₂ , frequency demodulators 6 ₃ and 6 ₄ , shapers 7 ₁ and 7 ₂ logical levels of binary code.

The device operates as follows. The receiver receives the transmitted signal. At the information output 11 (figure 2) of the receiver restore the transmitted signal. He in the absence of interference coincides with the signal generated by the transmitting device, which is shown in figure 1 (plot t), borrowed from the prototype method [1]. The difference in the received signal from its transmitted analogue, shown in FIG. 1 by the diagram m), may be due to distortions caused by interference.

, которые представлены на фиг.1 эпюрами в) и г), где τ_c - длительность одного двоичного символа «1» или «0» (фиг.1, эпюра а)). Восстановленный информационный поток на выходе 11 приемника 1 (фиг.2) подают на объединенные входы блоков 10₁ и 10₂ демодуляции сигналов, соответственно. При этом полосовые фильтры 2₁ и 2₂ обеспечивают разделение принятого единого сигнала на две составляющие передаваемых несущих частот, в результате чего производят выделение первой

(13₁) и второй

(13₂) несущих частот передатчика (надстрочный знак в виде (*) означает, что принятые частоты первой f₁ и второй f₂ несущих при передаче, рассматриваемой в общем случае, искажены помехами. Затем в хронизаторах 3₁ и 3₂ производят сравнение выделенных из группового сигнала первой

(13₁) и второй

(13₂) несущих частот передатчика с эталонными их значениями f₁ и f₂, формируемыми подстраиваемыми генераторами 4₁ и 4₂ частот. Для этого вырабатываемые в хронизаторах 3₁ и 3₂ соответствующие сигналы рассогласования

и

используют для обеспечения подстройки генераторов 4₁ и 4₂ частот до получения синусоидальных колебаний

и

, которые формируют на выходах 15₁ и 15₂. На втором выходе каждого из хронизаторов 3₁ и 3₂ формируют синхронизирующие импульсы (эпюра 14₁, приведенная на фиг.3), на основе которых в коммутаторах 5₁ и 5₂ сигналов определяют интервалы времени, в которых промежутки в переданном сигнале, вызванные отсутствием одной из частот f₁ и f₂, заполняют подстановкой частоты, формируемой подстраиваемыми генераторами 4₁ и 4₂ частот. Эту операцию производят до получения непрерывного фазоманипулированного сигнала по каждой из частот

и

.At the second synchronizing output 12 (figure 2) of the receiver, synchronizing pulses are generated, which follow with a period

, which are shown in FIG. 1 by diagrams c) and d), where τ _c is the duration of one binary symbol “1” or “0” (figure 1, diagram a)). The restored information stream at the output 11 of the receiver 1 (figure 2) is fed to the combined inputs of blocks 10 ₁ and 10 ₂ signal demodulation, respectively. In this case, the bandpass filters 2 ₁ and 2 ₂ provide the separation of the received single signal into two components of the transmitted carrier frequencies, as a result of which the first

(13 ₁ ) and the second

(13 ₂ ) the carrier frequencies of the transmitter (a superscript in the form of (*) means that the received frequencies of the first f ₁ and second f ₂ carriers in the transmission, which is considered in the general case, are distorted by interference. Then, in the chroniclers 3 ₁ and 3 ₂ , the selected from the group signal first

(13 ₁ ) and the second

(13 ₂ ) the carrier frequencies of the transmitter with their reference values f ₁ and f ₂ formed by tunable generators 4 ₁ and 4 ₂ frequencies. For this, the corresponding mismatch signals generated in the chronizers 3 ₁ and 3 ₂

and

used to ensure tuning of the generators 4 ₁ and 4 ₂ frequencies to obtain sinusoidal oscillations

and

which form at the outputs 15 ₁ and 15 ₂ . At the second output of each of the chronizers 3 ₁ and 3 ₂ , synchronizing pulses are generated (diagram ₁ , shown in Fig. 3), on the basis of which time intervals are determined in the switches 5 ₁ and 5 _{2 of the} signals, in which the intervals in the transmitted signal, caused by the absence of one of the frequencies f ₁ and f ₂ is filled with a frequency substitution generated by the tunable frequency generators 4 ₁ and 4 ₂ . This operation is performed until a continuous phase-shifted signal is obtained at each frequency

and

.

из-за того, что в это время передавалась и была принята несущая частота

. Аналогичным образом, работает коммутатор 5₂ сигналов: он заполняет промежутки времени, дополняя принятую несущую частоту

синусоидальным ее аналогом, вырабатываемым генератором 4₂ частот. В результате этого на выходах 16₁ и 16₂ будут сформированы непрерывные сигналы несущих частот

и

, где ∪ - знак логического объединения - означает, что частоты

и

дополняют принятые частоты

и

во время их отсутствия в передаваемом сигнале из-за передачи другой частоты, а

и

- подставленные и корректируемые под принимаемый сигнал синусоиды, формируемые генераторами 4₁ и 4₂ частот.So, for example, in relation to the first carrier frequency f _{1, the} switch 5 _{1 of the} signals provides the filling of time gaps associated with the absence of a carrier frequency

due to the fact that at this time the carrier frequency was transmitted and received

. Similarly, the switch 5 ₂ signals works: it fills the time intervals, supplementing the received carrier frequency

its analog sinusoidal generated by the generator ₄ February frequencies. As a result of this, continuous carrier signals will be generated at outputs 16 ₁ and 16 ₂

and

, where ∪ is the sign of the logical union - means that the frequencies

and

complement accepted frequencies

and

during their absence in the transmitted signal due to the transmission of a different frequency, and

and

- substituted and corrected for the received signal sinusoids generated by the generators 4 ₁ and 4 ₂ frequencies.

и

подвергают сравнению с соответствующими синусоидальными сигналами

и

, вырабатываемыми генераторами 4₁ и 4₂ частот (фиг.2). Надстрочные символы в виде (**) означают, что

и

являются частотами, которые подстраивают под копии сигналов

и

, принятые приемником на фоне помех.Figure 3 presents the plot 16 ₁ restored in its original form, the signal of the first carrier frequency, which is an analogue of the plot n), shown in figure 1, borrowed from the description of the prototype method [1]. A similar appearance will be absent in figure 3 diagram 16 ₂ . Its difference will consist only in a higher carrier frequency f ₂ . Further, the generated continuous signals of the carrier frequencies are supplied to phase demodulators 6 ₁ and 6 ₂ , the operation of which does not differ from their analogs currently used. In them incoming signals

and

subjected to comparison with the corresponding sinusoidal signals

and

generated by generators 4 ₁ and 4 ₂ frequencies (figure 2). Superscript characters in the form (**) mean that

and

are frequencies that adjust to copy signals

and

received by the receiver in the background of interference.

и

, формируемых генераторами 4₁ и 4₂ частот, и принятого сигнала

и

считают, что сигнал на выходах 18₁ и 18₂, соответственно, является синфазным. На эпюре 15₁ его условно обозначают квадратной скобкой снизу и называют «синусоидами» (эпюра 17₁, фиг.3). Если же фазы сравниваемых колебаний противоположные, то формируют сигнал на выходах 17₁ и 17₂. На эпюре 15₁, представленной на фиг.3, его условно обозначают квадратной скобкой сверху и называют «косинусоидами» (эпюра 18₁, фиг.3).In case of coincidence of the compared phases of frequencies

and

generated by the generators 4 ₁ and 4 ₂ frequencies, and the received signal

and

consider that the signal at the outputs 18 ₁ and 18 ₂ , respectively, is in-phase. On the diagram 15 ₁ it is conventionally indicated by a square bracket below and is called "sinusoids" (diagram 17 ₁ , figure 3). If the phases of the compared oscillations are opposite, then they form a signal at the outputs 17 ₁ and 17 ₂ . In the diagram 15 ₁ shown in FIG. 3, it is conventionally designated with a square bracket on top and is called “cosine waves” (diagram 18 ₁ , FIG. 3).

In the diagrams 17 ₁ and 18 ₁ shown in Fig. 4, signals 17 ₁ and 18 _{1 are} presented in the form of bipolar pulses for clarity of the process of generating the reconstructed video code, which are then combined into a single video signal 19 ₃ and 19 ₄ at the outputs of the frequency demodulators 6 ₃ and 6 ₄ .

Based on the received signals at the outputs 17 ₁ and 17 ₂ , 18 ₁ and 18 ₂ phase demodulators 6 ₁ and 6 ₂ restore the sequence of logical levels of the binary code, which in the absence of errors in the transmission and reception of information fully correspond to the converted video code (figure 1, diagrams and ), k)) [1], which on the transmitting side produce phase modulation of the first and second signal carriers. This is evidenced by diagrams 19 ₁ and 19 ₂ shown in figure 3. If there are no errors in the reception of the plot (19 ₁ and 19 ₂ ), shown in figure 3, correspond to the original illustrations presented in figure 1, diagrams a) and b) [1].

The recovery algorithm is illustrated by diagrams 17 ₁ , 18 ₁ and 19 ₁ shown in FIG. 3. The first carrier frequency f ₁ adopted by the receiver 1, modulated in phase (plot 16 ₁ ), is compared with a sinusoid formed by the frequency generator 4 ₁ (FIG. 2), and the time moments associated with the change are determined using frequency demodulators 6 ₃ and 6 ₄ frequencies f ₁ and f ₂ . The time intervals associated with the transmission of the first carrier frequency f ₁ are marked, for example, by the formation of a negative pulse (diagrams 15 ₁ and 18 ₁ shown in FIG. 4), and when the second carrier frequency f _{2 is} transmitted, a positive pulse is generated (diagrams 15 ₁ and 17 ₁ shown in FIG. 4). After inverting the negative pulses (plot 18 ₁ , FIG. 4) and adding them to the positive pulse sequence (plot 17 ₁ , FIG. 4), the first sequence of logical levels is formed by the generator 7 _{1 of the} logical levels of the binary code (plot 19 ₃ , FIG. 4) . Similarly, using the frequency demodulator 6 ₄ , the second sequence of logical levels is formed by the generator 7 _{2 of the} logical levels of the binary code (Fig. 4, plot 19 ₄ ).

и

, где τ_c - длительность одного двоичного символа «1» или «0» (фиг.1, эпюра а)). При последующей коррекции всю последовательность логических уровней, соответствующих символам «1» или «0» двоичного кода, представляют в виде целых значений τ_c, в результате чего формируют символы «1» или «0», составленные из двух импульсов продолжительностью

(фиг.4, эпюры 19₃ и 19₄). При этом на выходе 19₃ (фиг.3 и фиг.4) смена 1 высокого логического уровня на низкий, длительность которых равна

, соответствует двоичному символу «0», а переход от низкого уровня к высокому определяет передачу символа «1». На выходе 19₄ (фиг.3 и фиг.4) логический видеосигнал формируют в инверсном виде. В результате этого при отсутствии ошибок на выходах сумматоров 8₁ и 8₂ высокие и низкие уровни сформированных видеокодов компенсируют друг друга. При этом на выходах 20 и 21 при отсутствии ошибок устанавливается постоянный уровень.Restored by the frequency demodulators 6 ₃ and 6 _{4, the} logical levels of the binary code (Fig. 4, diagrams 19 ₃ and 19 ₄ ) become similar to the initial first sequence of logical levels of the binary code, presented on the diagram a) of figure 1 in a direct form, and on the diagram b) figure 1 in inverse form, respectively. Allowed differences are associated with the possibility of the appearance of logical levels corresponding to

and

where τ _c is the duration of one binary symbol "1" or "0" (Fig. 1, diagram a)). During subsequent correction, the entire sequence of logical levels corresponding to the symbols “1” or “0” of the binary code is represented as integer values of τ _c , as a result of which the symbols “1” or “0” are formed, composed of two pulses of duration

(figure 4, diagrams 19 ₃ and 19 ₄ ). In this case, at the output 19 ₃ (Fig. 3 and Fig. 4), a change of 1 high logical level to low, the duration of which is

corresponds to the binary character "0", and the transition from low to high determines the transmission of the character "1". At the output 19 ₄ (FIG. 3 and FIG. 4), a logical video signal is generated in inverse form. As a result of this, in the absence of errors at the outputs of the adders 8 ₁ and 8 _{2, the} high and low levels of the generated video codes cancel each other out. In this case, at the outputs 20 and 21 in the absence of errors, a constant level is set.

, будут отмечены одиночные ошибки, а импульсами, имеющими продолжительность

, будут обозначены места группирования k ошибок (эпюра 20, фиг.4). Для исправления обнаруженных ошибок используют результаты демодуляции переданных сообщений частотными демодуляторами 6₃ и 6₄. На выходе формирователя 9 формируют в соответствии с принятым правилом окончательный (обобщенный) поток переданной информации, представленный в виде двоичного кода. Если частотная демодуляция выполнена без ошибок, то на выходе 21 (фиг.2) второго сумматора 8₂ также будет «нулевой» сигнал. При наличии ошибок на выходе 21 появятся импульсы по аналогии с ранее рассмотренной иллюстрацией, представленной на эпюре 20, фиг.4. Но поскольку принимаемый сигнал демодулируют посредством различных демодуляторов (фазового и частотного), то ошибки на выходах 20 и 21 (фиг.2) будут, как правило, некоррелированными. Коррелированность ошибок может наблюдаться только при крайне низком соотношении сигнал/шум на входе приемника 1.On the diagrams 19 _3osh , 19 _4osh , shown in figure 4, the case is presented when, due to transmission errors and phase demodulation of signals, the generated video code sequences also differ from the transmitted signals. In this case, errors are marked with a “×”. As a result, at the output 20 of the adder 8 _{1, the} places of errors will be marked by pulses, while the pulse, the duration of which is equal to

, single errors will be marked, and pulses having a duration

, the places of grouping k errors will be indicated (plot 20, Fig. 4). To correct the detected errors, the results of demodulation of the transmitted messages using frequency demodulators 6 ₃ and 6 _{4 are used} . At the output of the shaper 9, the final (generalized) stream of transmitted information, presented in the form of a binary code, is formed in accordance with the adopted rule. If the frequency demodulation is performed without errors, then the output 21 (figure 2) of the second adder 8 ₂ will also be a "zero" signal. If there are errors at the output 21, pulses will appear by analogy with the previously considered illustration presented on the plot 20, Fig.4. But since the received signal is demodulated through various demodulators (phase and frequency), the errors at the outputs 20 and 21 (Fig. 2) will, as a rule, be uncorrelated. Error correlation can be observed only with an extremely low signal-to-noise ratio at the input of receiver 1.

If there are errors at the output of the frequency demodulator (output 21, Fig. 2) and there is no error signal at the output of the phase demodulator (plot 20, Fig. 4) in the generator 9 of the generalized bit stream of the transmitted information, preference will be given to the results of detecting the received signal using the phase demodulator (output 22, figure 2). In the opposite case, the output 22 of the shaper 9 will receive data only from the frequency demodulators 6 ₃ and 6 ₄ .

To correct errors, the rule of majority choice of matching values, called “2 of 3”, can also be used. For this, for example, one of the recovered copies of the transmitted information is excluded in turn and a vote is taken according to the “2 of 3” rule. The resulting three new copies of the transmitted information are again processed according to the majority rule “2 out of 3”. Matched two copies are considered reliable.

Thus, the device that implements the method according to claim 1, contains a receiver, two adders, a generator of a generalized bit stream of transmitted information, as well as two signal demodulation units, each of which includes a bandpass filter, a clock and a frequency generator, as well as a signal switch , phase and frequency demodulators, as well as a generator of logical levels of the binary code, the information output of the receiver is connected to the first input of the block connected to the input of the bandpass filter, which through a chronizer has a second syn the resetting input and the second synchronizing output are connected to the frequency generator, while the information input of the chronizer is combined with the first input of the signal switch, the output of which is connected to the first input of the phase demodulator combined with the input of the frequency demodulator, the second combined inputs of the chronizer, signal switch and phase demodulator are connected to the output of the frequency generator, two outputs of the phase demodulator are connected to the corresponding inputs of the generator of the logical levels of the binary code, synchronization the synchronizing third input of which is combined with the synchronizing third inputs of the signal switch and the phase demodulator and is connected to the second output of the chronizer, the synchronizing input of which is the second input of the block and connected to the synchronizing output of the receiver, the output of the logic level generator of the binary code is the first output of the block, and the output of the frequency demodulator its second output, while the first output of the first signal demodulation unit is connected to the first input of the first adder and the first input of the of the generalized bit stream of the transmitted information, the second output of the first block of signal demodulation is connected to the first input of the second adder and the second input of the generator of the generalized bit stream of transmitted information, the first output of the second block of demodulation signals is connected to the second input of the first adder and the third input of the generalized bit stream of transmitted information , the second output of the second block of signal demodulation is connected to the second input of the second adder and the fourth input of the generator of the generalized bit stream of the transmitted information, the output of the first adder is connected to the fifth input of the generator of the generalized bit stream of the transmitted information, the sixth input of which is connected to the output of the second adder.

To reduce out-of-band emissions when using the present invention, the first derivative is provided with continuity of the first derivative of the frequency-modulated signals generated for transmission at the boundaries of the symbols “0” and “1”. This can be achieved by transferring the moment of transition from one symbol, for example, “0”, to another “1” (opposite), not in the middle of the sine wave of the radio wave, but at its top, when their derivatives obtained from the previous signal of the same frequency and the signal of a different frequency, replacing it, is equal.

The present invention can be used to increase the energy potential of the Bort-Earth radio line when transmitting telemetric information (TMI) from launch vehicles (LV), booster blocks (RB) and spacecraft (SC) in the conditions of their testing and regular operation (SH ) It forms the basis for the construction of a new adaptive system of information and telemetry support (SITO) tests and SHE rocket and space technology (RKT), the effectiveness of which is improved by using the new technology of modulation of transmitted signals. The technical result consists in the compression of signals in the communication channel due to the simultaneous use of frequency and phase manipulation of the carrier frequency of the transmitter.

The present invention has the following essential characteristics. When applying the invention, an increase in the energy of transmitted TMI bits by 4-7 dB will be provided. In addition, it will provide additional ability to detect and correct errors without introducing redundancy in the transmitted symbols through the use of dual modulation of the carrier frequency. The signal compression in the communication channel is an analogue of the known data compression technology. Its fundamental difference lies in the fact that compression is carried out not at the level of binary code and video signals, but in the subsequent information transmission path oriented to radio signals and involving modulation of the transmitter carrier frequency.

When receiving information using the process of decompression of signals, which is the opposite of the conversion carried out on the transmitting side. As a result of the decompression of the signals, four copies of the transmitted data stream with independent errors are formed. At the same time, they provide the opportunity not only to control the integrity and reliability of the transmitted information under the influence of interference of various origins, but also create conditions for correcting errors.

The simulation performed in relation to the actual launch conditions of launch vehicles shows that when using the invention, the zone of reliable reception of telemetry data by one telemetry station will be increased by at least 2 times under constant other conditions (signal radiation power, bandwidth of the communication channel, interference model and reception conditions).

Previously, to create such a technical effect, it was necessary to install several sets of transmitting equipment and use different ranges of radio waves to distinguish them between receiving and recording stations. The proposed method of signal compression at one carrier frequency allows you to create duplicate information flows only due to new modulation technologies without increasing the number of transmitting devices.

As a result of this, without the introduction of additional devices and the use of high-performance antenna systems (YOU), the effectiveness of the information and telemetry support (SITO) testing system and RWE CT will be significantly increased. There will also be a beginning for the transition to adaptive systems of telemetry and data transmission, the effectiveness of which will increase by increasing the level of artificial intelligence created by the ability to implement new ideas and technologies.

Thus, a technical result is achieved, consisting in the following:

- in the compression of signals in the communication channel and the extension on this basis of its bandwidth;

- in ensuring control and correction of errors caused by interference of various origins;

- to increase the equivalent energy of binary code symbols due to repetitions and error correction.

Claims (3)

1. A method of transmitting information, which consists in collecting signals from message sources, synchronizing them in time, generating a compressed signal from synchronized collected signals, generating a signal of the first carrier frequency, phase manipulating the signal of the first carrier frequency with a compressed signal, transmitting the modulated signal over the communication channel, which form the signal of the second carrier frequency, form a periodic sequence of a pulsed signal of the meander type with a pulse duration half that of the pulse width of the compressed signal, phase-shift keying of the second carrier signal is performed by the compressed signal, the modulated signal to be transmitted via the communication channel is formed by frequency-shift keying of the phase-manipulated signals of the first and second carrier frequencies by a pulse-phase-shift periodic signal, characterized in that the signals are simultaneously extracted when receiving information the first and second carrier frequencies, each of which is phase-modulated by digital c the uppp signal, form copies of the first and second carrier frequencies by local generators, which are tuned to the received carrier frequencies based on the corresponding mismatch signals generated, fill in the interruptions associated with the transmission of another carrier frequency at this time, by adding carrier frequencies of local oscillators of the corresponding frequency until continuous in time of carriers of the first and second frequencies of information transmission, they are subjected to simultaneous phase demodulation, as a result of which direct The actual and inverse copies of the video signals with binary coding logic adopted for the transmission of information are used to control the integrity and reliability of the transmitted messages based on the addition of the generated direct and inverse copies of the video signals with logical levels of the binary code adopted for the transmission of information, which are simultaneously restored upon receipt of time-continuous carriers the first and second frequencies of information transmission are subjected to frequency demodulation, as a result of which direct and inverse copies of the video are also formed Ignals with binary coding logic, which was used before modulating the signals in the transmitting device, control the integrity and reliability of the transmitted messages based on the addition of direct and inverse copies of video signals with binary coding logic adopted to transmit information that was used before modulating the signals in the transmitting device, based on the received four signal copies of the transmitted information and the generated signs of monitoring the integrity and reliability of the transmitted messages correcting t transmission errors and formed in binary code transmitted by a single stream of error corrected information. 2. The method according to claim 1, characterized in that during the transmission of information, the first derivative is continuous for the frequency-modulated signals generated for transmission at the boundaries of the logical levels of the symbols “0” and “1” of the binary code by transferring the moment of transition from one symbol to another the opposite), not in the middle of the sine wave of the radio wave, but on its top, the equality of the derivatives obtained from the previous signal of one frequency, when switching to a signal of a different frequency that comes to replace it, is used to reduce the required bandwidth of the communication channel or to increase the speed of information transfer while maintaining the previous requirements for it. 3. The device that implements the method according to claim 1, containing a receiver, two adders, a generator of a generalized bit stream of transmitted information, as well as two signal demodulation units, each of which includes a bandpass filter, a clock and a frequency generator, as well as a signal switch, phase and frequency demodulators, as well as a logic level generator of the binary code, the information output of the receiver is connected to the first input of the block connected to the input of the bandpass filter, which is connected to the frequency generator through the chronizer, the input of the chronizer is combined with the first input of the signal switch, the output of which is connected to the first input of the phase demodulator, combined with the input of the frequency demodulator, the second combined inputs of the chronizer, signal switch and phase demodulator are connected to the output of the frequency generator, two outputs of the phase demodulator are connected to the corresponding inputs generator of logical levels of binary code, the synchronizing third input of which is combined with the synchronizing third inputs of the chronizer, commutation a torus of signals and a phase demodulator, is the second input of the block and is connected to the synchronizing output of the receiver, the output of the logic level generator of the binary code is the first output of the block, and the output of the frequency demodulator is its second output, while the first output of the first block of signal demodulation is connected to the first combined inputs the first adder and generator of the generalized bit stream of the transmitted information, the combined second inputs of which are connected to the first output of the second block of signal demodulation, second the outputs of the blocks are connected to the third and fourth inputs of the generator of the generalized bit stream of the transmitted information, respectively, which are simultaneously the first and second inputs of the second adder, the outputs of the first and second adders are connected to the fifth and sixth inputs of the generator of the generalized bit stream of the transmitted information, respectively, the output of which is the output devices.

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