RU2568390C1 - Method of generation and frequency-modulation of high-frequency signals and device for its implementation - Google Patents

Abstract

FIELD: radio engineering, communication.

SUBSTANCE: method of generation and frequency modulation of high-frequency signals is offered. The method is based on interaction of high-frequency signal with the feed-forward path formed by a triple-pole nonlinear element and a four-pole network, a load and an external feedback circuit, fulfilment of conditions of excitement in the form of balance of amplitudes and balance of phases pre-determining respectively amplitude and frequency of the generated high-frequency signals, conditions of matching of the feed-forward path with the load and conditions of matching of load with the control electrode of the triple-pole nonlinear element, change of frequency of the generated signal by the law of change of amplitude of the low-frequency control signal, differing in that the feed-forward path is formed by the cascade connected complex four-pole network and a triple-pole nonlinear element.

EFFECT: increase of range of generated oscillations in the pre-set range of change of amplitude of the control signal.

2 cl, 3 dwg

Description

The invention relates to the field of radio communications and electronic warfare can be used to create devices for the generation and frequency modulation of high-frequency signals, which allows you to generate frequency-modulated signals according to a given law for radio communications with increased noise immunity and complex signals for electronic warfare.

A known method of generating and frequency modulating a high-frequency signal, based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, the organization of external positive feedback between the load and the control electrode of the first nonlinear element, the fulfillment of the excitation conditions in the form of a balance of amplitudes and phase balance, respectively determining the amplitude and the frequency of the generated high-frequency signal, and the conditions for matching the first non-linear element with the load, change frequency of the generated high-frequency signal by changing the phase balance by changing the parameter of the second nonlinear element included in the selective load, according to the law of changing the amplitude of the low-frequency control (primary, information) signal (see IS Gonorovsky, Radio engineering circuits and signals. - M: “ Bustard ", - 2006, p. 434-437).

A device for generating and frequency modulating a high-frequency signal, consisting of a constant voltage source that sets the operating point in the middle of the quasilinear section of the current-voltage characteristic of the transistor, a four-terminal reactive load, in the form of a parallel oscillatory circuit, which includes a varicap connected to the control signal source, RC- external positive feedback circuit between the load and the control electrode of the transistor, while the parameters of the circuit, transi the store and the varicap are selected from the condition of providing the specified amplitude and frequency range of the generated high-frequency signal according to the law of changing the amplitude of the low-frequency control (primary, information) signal (see Gonorovsky IS Radio engineering circuits and signals. - M: “Bustard”, - 2006 , p. 434-437).

The principle of operation of this device is as follows. When a constant voltage (current) source is turned on, due to an abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of a positive feedback circuit, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is supplied to the control electrode of the transistor, which, by matching with the reactive four-terminal device, starts to operate in the amplification mode until the amplitude of this oscillation increases to the level at which saturation mode (amplitude limits). There is a stationary mode. In this mode, a change in the capacitance of a varicap under the action of a control signal leads to a change in the frequency of the generated signal according to the law of change in the amplitude of the low-frequency signal.

The closest in technical essence and the achieved result (prototype) is a method for generating and frequency modulating a high-frequency signal, based on converting the energy of a constant voltage source into the energy of a high-frequency signal, organizing internal feedback in the first non-linear element by using a bipolar non-linear element with negative differential resistance, the fulfillment of the excitation conditions in the form of a balance of amplitudes and a balance of phases that determine accordingly, the amplitude and frequency of the generated high-frequency signal, and the conditions for matching the first non-linear element with the load, changing the frequency of the generated high-frequency signal by changing the phase balance by changing the parameter of the second non-linear element included in the selective load, according to the law of changing the amplitude of the low-frequency control (primary, information) signal (see. Honorovsky I.S. Radio engineering circuits and signals. - M: “Bustard”, - 2006, p. 414-417, 434-437).

The closest in technical essence and the achieved result (prototype) is a device for generating and frequency modulating a high-frequency signal, consisting of a constant voltage source that sets an operating point in the middle of the falling section of the voltage-current characteristic of a bipolar nonlinear element with negative differential resistance, reactive four-terminal, parallel load oscillatory circuit with varicap turned on, connected to the source of the control signal and, at the same time, the parameters of the circuit, the bipolar nonlinear element, and the varicap are selected from the condition of ensuring the given amplitude and frequency range of the generated high-frequency signal according to the law of amplitude variation of the low-frequency control (primary, information) signal (see I. Gonorovsky, Radio engineering circuits and signals. - M: “Bustard”, - 2006, p. 414-417, 434-437). The principle of operation of this device is as follows. When a constant voltage (current) source is turned on, due to an abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of internal feedback in a bipolar nonlinear element, a negative differential resistance arises in the section with a falling current-voltage characteristic, which, by matching with a reactive four-terminal, compensates for losses in the circuit. Due to this, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is amplified until the amplitude of this oscillation increases to a level at which the amplitude goes beyond the falling section of the current-voltage characteristic. There is a stationary mode. In this mode, a change in the capacitance of a varicap under the action of a control signal leads to a change in the frequency of the generated signal according to the law of change in the amplitude of the low-frequency signal.

The disadvantage of these methods and devices is the presence of two nonlinear elements, one of which works as an amplifier and a limiter, and the second is used to change the frequency of the generated high-frequency signal and a small linear section of the modulation characteristic due to the smallness of the linear section of the capacitance-voltage characteristic of the varicap. In addition, it does not indicate how it is necessary to choose the values of the parameters of the four-terminal networks, at which the excitation mode and the stationary mode occur. This question arises especially sharply when designing generation and frequency modulation devices in the HF and UHF bands, on which the reactive components of the parameters of nonlinear elements must be taken into account. Currently, the classical theory of radio circuits does not take this into account. Moreover, with the help of reactive four-terminal it is not always possible to provide the conditions for the generation, since they have certain areas of physical feasibility (areas of variation of the real and imaginary components of the load resistance), within which the matching conditions are realized (A. Golovkov. Complex electronic devices. M .: Radio and communications, 1996. - 128 p.).

The technical result of the invention is the generation and frequency modulation of a high-frequency signal with an increased linear portion of the frequency modulation characteristic using a single non-linear element, which allows you to create efficient compact devices for generating and frequency modulation, as well as increasing the range of generated oscillations in a given range of changes in the amplitude of the control signal and increasing the area physical feasibility.

1. The specified result is achieved by the fact that in the known method of generating and frequency modulating high-frequency signals, based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, the interaction of a high-frequency signal with a direct transmission circuit made of a three-pole nonlinear element and a four-pole, load and external circuit feedback, the fulfillment of the excitation conditions in the form of a balance of amplitudes and a balance of phases, which determine respectively the amplitude and frequency of the generated high-frequency signals, conditions for matching the direct transmission circuit with the load and conditions for matching the load with the control electrode of a three-pole nonlinear element, changing the frequency of the generated signal according to the law of changing the amplitude of the low-frequency control signal, additionally, the direct transmission circuit is made of cascade-connected complex four-pole and three-pole non-linear element, the load performed in the form of a first two-terminal with complex resistance, as an external feedback circuit the ides use an arbitrary complex four-terminal network connected in parallel to the direct transmission circuit, the direct transmission circuit and the feedback circuit as a single node cascade between the introduced second two-terminal network with complex resistance simulating the resistance of the signal source of the generator and the frequency modulator in amplification mode and the load, in the interests of the implementation of frequency modulation of the excitation condition in the form of a balance of amplitudes and phase balance and matching conditions are sequentially performed in a given band often t and the corresponding range of the amplitude of the low-frequency control signal by choosing the frequency dependences of the imaginary components of the resistance of the first x _n and second x ₀ two-terminal with complex resistances from the condition of providing a stationary generation mode in the form of equal to zero denominator of the gain in the given frequency band and the corresponding the range of the amplitude of the low-frequency control signal in accordance with the following mathematical expressions:

B=a₁d₂+c₁b₂-a₂d₁-c₂b₁-2r₀[d₁c₂+c₁d₂];

B = a ₁ d ₂ + c ₁ b ₂ -a ₂ d ₁ -c ₂ b ₁ -2r ₀ [d ₁ c ₂ + c ₁ d ₂ ];

|y|=y₁₁y₂₂-y₁₂y₂₁;

| y | = y ₁₁ y ₂₂ -y ₁₂ y ₂₁ ;

|a|=a₁₁a₂₂-a₁₂a₂₁;

| a | = a ₁₁ a ₂₂ -a ₁₂ a ₂₁ ;

, $$y_{12}^{VT}$$

, $$y_{21}^{VT}$$

, $$y_{22}^{VT}$$

- заданные зависимости комплексных элементов матрицы проводимостей трехполюсного нелинейного элемента в цепи прямой передачи от частоты генерируемого сигнала и амплитуды низкочастотного сигнала; $$y_{11}^{OC}$$

, $$y_{12}^{OC}$$

, $$y_{21}^{OC}$$

, $$y_{22}^{OC}$$

- заданные частотные зависимости комплексных элементов матрицы проводимостей комплексного четырехполюсника цепи обратной связи; r_н, r₀ - заданные частотные зависимости действительных составляющих комплексных сопротивлений нагрузки и сопротивления источника сигнала устройства генерации и частотной модуляции в режиме усиления.where a ₁ = Re (a _o ), a ₂ = Im (a _o ), b ₁ = Re (b _o ), b ₂ = Im (b _o ), c ₁ = Re (c _o ), c ₂ = Im (c _o ), d ₁ = Re (d _o ), d ₂ = Im (d _o ) are the frequency dependences of the real and imaginary components of the unnormalized elements of the classical transmission matrix of the entire device; a, b, c, d - given frequency dependences of the complex elements of the classical transmission matrix of a complex four-terminal network in a direct transmission circuit at given frequencies; $$y_{\mathrm{eleven}}^{VT}$$

, $$y_{12}^{VT}$$

, $$y_{21}^{VT}$$

, $$y_{22}^{VT}$$

- the given dependences of the complex elements of the conductivity matrix of a three-pole nonlinear element in the direct transmission circuit on the frequency of the generated signal and the amplitude of the low-frequency signal; $$y_{\mathrm{eleven}}^{OC}$$

, $$y_{12}^{OC}$$

, $$y_{21}^{OC}$$

, $$y_{22}^{OC}$$

- given frequency dependences of the complex elements of the conductivity matrix of a complex four-terminal feedback loop; r _n , r ₀ - given frequency dependencies of the real components of the complex load resistances and the resistance of the signal source of the generation device and frequency modulation in the amplification mode.

2. This result is achieved by the fact that in the device for generating and frequency modulating high-frequency signals, consisting of a constant voltage source and a low-frequency control signal, a direct transfer circuit of a three-pole nonlinear element and a four-terminal, load and external feedback circuit, additionally, the direct transfer circuit is made of cascade-connected complex four-terminal and three-pole nonlinear element, the load is made in the form of the first two-terminal with complex resistance, as an external feedback circuit, an arbitrary complex four-terminal network connected in parallel to the direct transmission circuit is used, the direct transmission circuit and the feedback circuit as a single node are cascaded between the second integrated two-terminal circuit with a complex resistance simulating the resistance of the generator signal source and the frequency modulator in amplification mode, and load imaginary components of the first and second two-terminal networks with complex impedances z and z _{0n Hn} formed of sequential kolebatelnog circuit with parameters L _1k, C _1k, connected in parallel with inductance L _0k, values of parameters L _1k, C _1k, L _0k to ensure frequency modulation determined from the conditions for the realization of a stationary lasing in a vanishing denominator gain in the amplification mode in the three specified frequencies and the corresponding three values of the amplitude of the low-frequency control signal in accordance with the following mathematical expressions:

Where

B=a₁d₂+c₁b₂-a₂d₁-c₂b₁-2r_0n[d₁c₂+c₁d₂];

B = a ₁ d ₂ + c ₁ b ₂ -a ₂ d ₁ -c ₂ b ₁ -2r _0n [d ₁ c ₂ + c ₁ d ₂ ];

|y|=y₁₁y₂₂-y₁₂y₂₁;

| y | = y ₁₁ y ₂₂ -y ₁₂ y ₂₁ ;

|a|=a₁₁a₂₂-a₁₂a₂₁;

| a | = a ₁₁ a ₂₂ -a ₁₂ a ₂₁ ;

, $$y_{12n}^{VT}$$

, $$y_{21n}^{VT}$$

, $$y_{22n}^{VT}$$

- заданные значения комплексных элементов матрицы проводимостей трехполюсного нелинейного элемента в цепи прямой передачи на заданных частотах и соответствующих трех значениях амплитуды низкочастотного управляющего сигнала; $$y_{11n}^{OC}$$

, $$y_{12n}^{OC}$$

, $$y_{21n}^{OC}$$

, $$y_{22n}^{OC}$$

- заданные значения комплексных элементов матрицы проводимостей комплексного четырехполюсника цепи обратной связи на заданных частотах; r_нn, r_0n - заданные значения действительных составляющих комплексных сопротивлений нагрузки и сопротивления источника сигнала устройства генерации и частотной модуляции в режиме усиления на заданных частотах.ω _n = 2πf _n ; f _n - given frequencies; n = 1, 2, 3 - numbers of the given frequencies; k = 0, n is the index characterizing the resistance of the signal source of the generator and the frequency modulator in the amplification mode (k = 0) and load (k = n), respectively; a ₁ = Re (a _o ), and ₂ = Im (a _o ), b ₁ = Re (b _o ), b ₂ = Im (b _o ), c ₁ = Re (c _o ), c ₂ = Im ( c _o ), d ₁ = Re (d _o ), d ₂ = Im (d _o ) are the real and imaginary components of the unnormalized elements of the classical transfer matrix of the entire device; a _n , b _n , c _n , d _n - given values of the complex elements of the classical transmission matrix of a complex four-terminal network in a direct transmission circuit at given frequencies; $$y_{\mathrm{eleven}n}^{VT}$$

, $$y_{12n}^{VT}$$

, $$y_{21n}^{VT}$$

, $$y_{22n}^{VT}$$

- setpoints of the complex elements of the conductivity matrix of a three-pole nonlinear element in the direct transmission circuit at the given frequencies and the corresponding three values of the amplitude of the low-frequency control signal; $$y_{\mathrm{eleven}n}^{OC}$$

, $$y_{12n}^{OC}$$

, $$y_{21n}^{OC}$$

, $$y_{22n}^{OC}$$

- setpoints of the complex elements of the conductivity matrix of a complex quadrupole feedback circuit at given frequencies; r _nn , r _0n - set values of the real components of the complex load resistances and the resistance of the signal source of the device for generating and frequency modulation in the amplification mode at given frequencies.

In FIG. 1 shows a diagram of a device for generating and frequency modulating high-frequency signals (prototype) that implements the prototype method.

In FIG. 2 shows a structural diagram of the proposed device according to p. 2., which implements the proposed method according to p. 1.

In FIG. 3 shows reactive bipolar circuits implementing the imaginary components of the resistance of the generator signal source in the amplification mode (k = 0) and the load (k = n) included in the circuit shown in FIG. 2.

The prototype device (Fig. 1), which implements the prototype method, contains a nonlinear element - 1 with negative differential resistance, connected to a voltage source - 2 with low internal resistance, matching filtering device - 3 (reactive four-terminal), the load is in the form of an oscillatory circuit on the elements L - 4, R - 5, C (t) - 6. The controlled capacitance C (t) realized by the varicap - 6 is connected to the source of the low-frequency control (information) signal - 7. The principle of operation of the device for generating and modulating high-frequency s signals (prototype) that implements the prototype method is as follows.

When you turn on the constant voltage source - (2) due to the abrupt change in the amplitude in the entire circuit, oscillations arise, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of internal feedback, in a bipolar nonlinear element, for example, a tunneling diode - 1, a negative differential resistance appears in the section with a falling current-voltage characteristic, which, by matching with a reactive four-terminal - 3, compensates for losses in the circuit L - 4, R - 5 , С (t) - 6. Owing to this, the oscillation with a frequency equal to the resonant frequency of the oscillating circuit is amplified until the amplitude of this oscillation increases to a level at which the amplitude goes beyond affairs of the falling section of the current-voltage characteristic. There is a stationary mode. In this mode, a change in the capacitance of the varicap C (t) - 6 under the action of the control signal of the source - 7 leads to a change in the frequency of the generated signal according to the law of the amplitude of this signal.

, $$y_{12n}^{VT}=g_{12n}^{VT}+j{b}_{12n}^{VT}$$

, $$y_{21n}^{VT}=g_{21n}^{VT}+j{b}_{21n}^{VT}$$

, $$y_{22n}^{VT}=g_{22n}^{VT}+j{b}_{22n}^{VT}$$

на заданных частотах генерируемых сигналов и соответствующих амплитудах низкочастотного управляющего сигнала, подключенного к источнику постоянного напряжения и источнику низкочастотного управляющего сигнала - 2. Цепь прямой передачи из нелинейного элемента - 1 и четырехполюсника - 11 параллельно соединена по высокой частоте с цепью внешней обратной связи (входы соединены параллельно и выходы - параллельно), выполненной в виде произвольного комплексного четырехполюсника - 12, сформированного в общем случае на двухполюсниках с комплексными сопротивлениями. Цепь прямой передачи и цепь внешней обратной связи как единый узел каскадно включены по высокой частоте между источником входного высокочастотного сигнала в режиме усиления с оптимальными мнимыми составляющими сопротивлений z_0n=r_0n+jx_0n-13 на заданных частотах (второй комплексный двухполюсник), имитирующих сопротивление источника высокочастотных колебаний, возникающих при включении источника постоянного напряжения - 2 в момент скачкообразного изменения амплитуды его напряжения в режиме генерации, и нагрузкой - 14, с оптимальными мнимыми составляющими сопротивлений z_нn=r_нn+jx_нn на заданных частотах (первый двухполюсник с комплексным сопротивлением). Произвольный четырехполюсник - 12 тоже характеризуется известными значениями элементов матрицы проводимостей $$y_{11n}^{OC}=g_{11n}^{OC}+j{b}_{11n}^{OC}$$

, $$y_{12n}^{OC}=g_{12n}^{OC}+j{b}_{12n}^{OC}$$

, $$y_{21n}^{OC}=g_{21n}^{OC}+j{b}_{21n}^{OC}$$

, $$y_{22n}^{OC}=g_{22n}^{OC}+j{b}_{22n}^{OC}$$

на заданных частотах(n=1, 2, 3 - номер частоты). Мнимые составляющие сопротивлений z_0n, z_нn (второго и первого двухполюсников с комплексными сопротивлениями) реализованы (фиг. 3) из последовательного колебательного контура с параметрами L_1k - 15, C_1k - 16, параллельно соединенного с индуктивностью L_0k - 17. При k=0 имеем двухполюсник для формирования х₀. При k=н имеем двухполюсник для формирования х_н. Значения параметров L_1k - 15, C_1k - 16, L_0k - 17 определены из условия равенства нулю знаменателя коэффициента передачи на трех частотах и соответствующих трех амплитудах управляющего сигнала с помощью специальных математических выражений. Синтез генератора (выбор значений указанных параметров и схемы формирования этих двухполюсников (фиг. 3) осуществлен по критерию обеспечения баланса амплитуд и баланса фаз путем реализации равенства нулю знаменателя коэффициента передачи устройства генерации в режиме усиления последовательно на заданных частотах генерируемых сигналов при соответствующем изменении амплитуды низкочастотного управляющего сигнала. Выбор значений элементов матриц сопротивлений комплексных четырехполюсников - 11, 12 или их схем и значений параметров элементов, а также значений действительных составляющих первого и второго двухполюсников можно осуществлять произвольно или исходя из каких-либо других физических соображений. В данном изобретении эти значения выбираются из условий физической реализуемости. В режиме генерации и частотной модуляции источник входного высокочастотного сигнала отключается и вместо него устанавливается короткозамыкающая перемычка. Предлагаемое устройство функционирует следующим образом.The disadvantages of the prototype method and device for its implementation are described above. The proposed device according to p. 2 (Fig. 2), which implements the proposed method according to p. 1, contains a direct transmission circuit from a cascade-connected complex quadrupole - 11 with known elements of the classical transmission matrix a _n , b _n , c _n , d _n given frequencies of generated signals and a three-pole nonlinear element - 1 with known elements of the conductivity matrix; $$y_{\mathrm{eleven}n}^{VT}=g_{\mathrm{eleven}n}^{VT}+j{b}_{\mathrm{eleven}n}^{VT}$$

, $$y_{12n}^{VT}=g_{12n}^{VT}+j{b}_{12n}^{VT}$$

, $$y_{21n}^{VT}=g_{21n}^{VT}+j{b}_{21n}^{VT}$$

, $$y_{22n}^{VT}=g_{22n}^{VT}+j{b}_{22n}^{VT}$$

at specified frequencies of the generated signals and the corresponding amplitudes of the low-frequency control signal connected to a constant voltage source and a low-frequency control signal source - 2. The direct transmission circuit from a nonlinear element - 1 and a four-terminal - 11 is connected in parallel at high frequency to an external feedback circuit (inputs are connected in parallel and outputs - in parallel), made in the form of an arbitrary complex four-terminal - 12, formed in the general case on two-terminal with mi resistances. The direct transmission circuit and the external feedback circuit as a single unit are cascaded at a high frequency between the source of the high-frequency input signal in the amplification mode with optimal imaginary components of the resistance z _0n = r _0n + jx _0n -13 at given frequencies (second complex two-terminal network) simulating the resistance the source of high-frequency oscillations that occur when the DC voltage source is turned on - 2 at the time of an abrupt change in the amplitude of its voltage in the generation mode, and with a load of 14, with optimal imaginary resistance components z _нn = r _нn + jx _нn at given frequencies (the first two-terminal with complex resistance). An arbitrary four-terminal - 12 is also characterized by known values of the elements of the conductivity matrix $$y_{\mathrm{eleven}n}^{OC}=g_{\mathrm{eleven}n}^{OC}+j{b}_{\mathrm{eleven}n}^{OC}$$

, $$y_{12n}^{OC}=g_{12n}^{OC}+j{b}_{12n}^{OC}$$

, $$y_{21n}^{OC}=g_{21n}^{OC}+j{b}_{21n}^{OC}$$

, $$y_{22n}^{OC}=g_{22n}^{OC}+j{b}_{22n}^{OC}$$

at given frequencies (n = 1, 2, 3 - frequency number). The imaginary components of the resistances z _0n , z _нn (second and first two-terminal with complex resistances) are implemented (Fig. 3) from a series oscillatory circuit with parameters L _1k - 15, C _1k - 16, connected in parallel with the inductance L _0k - 17. At k = 0, we have a two-terminal network for the formation of x ₀ . When k = n, we have a two-terminal network for the formation of x _n . The values of the parameters L _1k - 15, C _1k - 16, L _0k - 17 are determined from the condition that the denominator of the transmission coefficient at three frequencies and the corresponding three amplitudes of the control signal be equal to zero using special mathematical expressions. The synthesis of the generator (the choice of the values of these parameters and the formation scheme of these two-terminal circuits (Fig. 3) was carried out according to the criterion of ensuring the balance of amplitudes and phase balance by implementing equal to zero denominator of the transmission coefficient of the generation device in the amplification mode sequentially at the given frequencies of the generated signals with a corresponding change in the amplitude of the low-frequency The choice of the values of the elements of the resistance matrices of complex quadrupoles - 11, 12 or their circuits and the values of the parameters of nt, as well as the values of the real components of the first and second two-terminal, can be carried out arbitrarily or on the basis of any other physical considerations.In the present invention, these values are selected from the conditions of physical realizability.In the generation and frequency modulation mode, the input high-frequency signal is turned off and set instead short-circuit jumper The proposed device operates as follows.

, $$y_{12}^{VT}=g_{12}^{VT}+j{b}_{12}^{VT}$$

, $$y_{21}^{VT}=g_{21}^{VT}+j{b}_{21}^{VT}$$

, $$y_{22}^{VT}=g_{22}^{VT}+j{b}_{22}^{VT}$$

и цели обратной связи $$y_{11}^{OC}=g_{11}^{OC}+j{b}_{11}^{OC}$$

, $$y_{12}^{OC}=g_{12}^{OC}+j{b}_{12}^{OC}$$

, $$y_{21}^{OC}=g_{21}^{OC}+j{b}_{21}^{OC}$$

, $$y_{22}^{OC}=g_{22}^{OC}+j{b}_{22}^{OC}$$

, от частоты. Элементы матрицы проводимостей трехполюсного нелинейного элемента зависят также от амплитуды низкочастотного управляющего сигнала. Таким образом, в качестве исходных данных используются значения элементов матрицы проводимостей трехполюсного нелинейного элемента на заданных частотах генерируемых сигналов, соответствующих определенным амплитудам низкочастотного управляющего сигнала. Нелинейный элемент описывается матрицей проводимостей и соответствующей матрицей передачи:When a constant voltage source-2 is turned on, due to an abrupt change in the amplitude, oscillations occur in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of external feedback and due to the indicated choice of the values of the parameters L _1k - 15, C _1k - 16, L _0k -17 and the circuits for the formation of two-terminal networks - 13, 14 (Fig. 3), the feedback becomes positive, which is equivalent to negative conductivity circuit (g ₂₁ or g ₁₂ ), which compensates for losses in the entire circuit at a given frequency. Therefore, the oscillation amplitudes with given frequencies are amplified to certain levels and then limited. Due to this, oscillations with a given frequency are amplified until the amplitudes of these oscillations increase to a level at which the amplitude goes beyond the quasilinear portion of the current-voltage characteristic of the passage. There is a stationary mode. In this mode, the change in the amplitude of the low-frequency signal of the source - 2 leads to a change in the frequency of the generated signal according to the law of change of this amplitude, that is, to frequency modulation. Since the quadripoles - 11, 12 are selected complex, this leads to an increase in the physical realizability of the stationary generation mode and frequency modulation in a given frequency band and a given range of variation in the amplitude of the low-frequency control signal. Let us prove the feasibility of implementing these properties. Let the direct transmission circuit, consisting of a cascade-connected interconnected three-pole nonlinear element and an inverter, connected to the feedback circuit in parallel (Fig. 2). Let us introduce the notation of the dependences of the resistance of the signal source in the amplification mode z ₀ = r ₀ + jx ₀ , the load z _n = r _n + jx _n and the known dependences of the elements of the conductivity matrices of a three-pole nonlinear element $$y_{\mathrm{eleven}}^{VT}=g_{\mathrm{eleven}}^{VT}+j{b}_{\mathrm{eleven}}^{VT}$$

, $$y_{12}^{VT}=g_{12}^{VT}+j{b}_{12}^{VT}$$

, $$y_{21}^{VT}=g_{21}^{VT}+j{b}_{21}^{VT}$$

, $$y_{22}^{VT}=g_{22}^{VT}+j{b}_{22}^{VT}$$

and feedback goals $$y_{\mathrm{eleven}}^{OC}=g_{\mathrm{eleven}}^{OC}+j{b}_{\mathrm{eleven}}^{OC}$$

, $$y_{12}^{OC}=g_{12}^{OC}+j{b}_{12}^{OC}$$

, $$y_{21}^{OC}=g_{21}^{OC}+j{b}_{21}^{OC}$$

, $$y_{22}^{OC}=g_{22}^{OC}+j{b}_{22}^{OC}$$

, from frequency. The elements of the conductivity matrix of a three-pole nonlinear element also depend on the amplitude of the low-frequency control signal. Thus, as the initial data, the values of the conductivity matrix elements of a three-pole nonlinear element at the given frequencies of the generated signals corresponding to certain amplitudes of the low-frequency control signal are used. A nonlinear element is described by the conductivity matrix and the corresponding transfer matrix:

Where

The complex four-terminal network (CC) is characterized by the well-known transfer matrix:

where a, b, c, d are complex elements of the classical transfer matrix.

For the direct transmission chain, the elements of the non-normalized classical transmission matrix are obtained by multiplying the transmission matrices (2) and (1):

The corresponding elements of the conductivity matrix of the direct transfer circuit (the second terms in (4)) and the elements of the conductivity matrix of the OS circuit are summed up:

where | a | = a ₁₁ a ₂₂ -a ₁₂ a ₂₁ .

Unnormalized transfer matrix elements of the entire device:

where | y | = y ₁₁ y ₂₂ -y ₁₂ y ₂₁ .

Taking into account the normalization conditions, we obtain the general normalized transfer matrix of the entire device:

Generator transfer function in gain mode:

The denominator (7) can be reduced to the form corresponding to the immitance stability criterion (Kulikovsky A.A. Stability of active linearized circuits with amplifiers of a new type. M-L .: SEI, 1962, 192 pp.):

The first term is the complex resistance of the passive part (the resistance of the signal source in amplification mode). The second term is the input resistance of the active part of the device (the rest of the generator to the right of z ₀ ). The immitance stability criterion (8) corresponds to the balance of amplitudes and phases (I. Gonorovsky, Radio engineering circuits and signals. M.: “Drofa”, 2006, p. 386):

$$\mathrm{one}-\frac{-(y_{22}^{OC}+\frac{a_{\mathrm{eleven}}}{a_{12}})z_n+\mathrm{one}}{[|y|z_n-(y_{\mathrm{eleven}}^{OC}+\frac{a_{22}}{a_{12}})]z_0}=0.\text{(9)}$$

Thus, the vanishing of the denominator of the transfer function corresponds to the stationary generation mode. From the fact that the denominator of the transmission coefficient in the amplification mode is equal to zero, one can find a restriction on any pair of the quantities used, for example, x ₀ , x _n

B=a₁d₂+c₁b₂-a₂d₁-c₂b₁-2r_0n[d₁c₂+c₁d₂];Where

B = a ₁ d ₂ + c ₁ b ₂ -a ₂ d ₁ -c ₂ b ₁ -2r _0n [d ₁ c ₂ + c ₁ d ₂ ];

The index n must also be introduced in other notation of physical quantities that explicitly depend on the frequency.

Solution (10) makes sense of the dependences of the quantities x ₀ , x _n on the frequency that are optimal according to the criterion for ensuring signal generation in the entire frequency spectrum while changing the amplitude of the low-frequency control signal. Resistances r _0n , r _нn can be chosen arbitrarily or on the basis of any other physical considerations.

To implement the optimal approximation (10) in a given frequency band and a given range of changes in the amplitude of the low-frequency signal, it is necessary to form each two-terminal network with resistances x ₀ , x _n of no less than Ν (n = 1, 2 ... Ν; N is the number of interpolation frequencies and the number of corresponding amplitudes of the low-frequency signal) of elements of type L, C, find expressions for their resistances, equate them to the optimal values of the resistance of two-terminal devices at given frequencies, determined by formulas (10), and solve the system thus formed N equations with respect to N selected parameters L, C for each two-terminal network. The values of the parameters of the remaining elements can be chosen arbitrarily or on the basis of any other physical considerations, for example, from the condition of physical realizability.

Let the imaginary components of the resistances of two-terminal devices with complex resistances z ₀ , z _{n be} formed from a series oscillatory circuit with parameters L _1k , C _1k , connected in parallel with the inductance L _0k . For k = 0, we have a two-terminal network for the formation of x ₀ . When k = n, we have a two-terminal network for the formation of x _n .

We compose two systems of three equations by equating the reactance of two-terminal devices (Fig. 3) in the form of a series oscillatory circuit connected inductance in parallel to the optimal values (10):

Decision:

where ω _n = 2πf _n; f _n - given frequencies; k = 0, n is an index characterizing the resistance of the signal source of the generator and the frequency modulator in the gain and load modes, respectively;

The implementation of optimal approximations of the frequency characteristics of the imaginary components of the resistance of the generator signal source in the gain and load mode (10) using (11), (12), provides the implementation of the condition of the balance of amplitudes and phase balance in series at all frequencies in the vicinity of three given frequencies with a simultaneous change in amplitude low-frequency signal in the vicinity of three corresponding specified amplitude values. A reasonable choice of frequency positions relative to each other increases the quasilinear portion of the frequency modulation characteristic. As a result, with a continuous (or discrete) change in the amplitude of the control signal, the frequency of the generated signal is changed according to the law of the amplitude of the low-frequency control low-frequency signal, that is, frequency modulation (or manipulation).

The proposed technical solutions are new because the method and device for generating and frequency modulating high-frequency oscillations that provide frequency modulation of high-frequency signals over a given range of variation of the frequency of the generated signal and the corresponding range of variation of the amplitude of the control signal when using arbitrary complex four-terminal circuits in a direct transmission circuit and feedback circuits and the first integrated bipolar as loads and the direct transmission circuit is made of a cascade-connected complex four-pole and three-pole nonlinear element and is connected to the feedback circuit in a parallel circuit (Fig. 2), while the resistance of the generator signal source in the amplification mode is realized by the second complex two-pole, and the imaginary components of the first and of the second complex two-terminal network, the reactive two-terminal networks of identical structure with generally different values of the parameters are implemented (Fig. 3). The values of the parameters of these two-terminal devices are selected in accordance with special mathematical expressions.

The proposed technical solutions have an inventive step, since it does not explicitly follow from the published scientific data and the known technical solutions that the claimed sequence of operations (execution of the generation and frequency modulation device in the form shown in Fig. 2, execution of four-terminal circuits in the direct transmission and reverse circuits complex communications, the use of integrated load (the first two-terminal integrated resistance), the formation of the resistance of the signal source of the frequency modulator mode gain in a second integrated two-terminal network, the implementation of the imaginary components of the first and second integrated two-terminal of the series resonant circuit with parameters L _1k, C _1k, connected in parallel with inductance L _0k, selection of these parameter values from the condition providing a stationary lasing at three frequencies, corresponding to the three amplitudes of the low-frequency control signal on a non-linear three-pole element, provides the formation of a high-frequency signal in the dynamics, changing the variation of its frequency in a given frequency band according to the law of changing the amplitude of the source of the control signal (frequency modulation) and the expansion of the field of physical realizability.

The proposed technical solutions are practically applicable, since nonlinear three-pole elements (lamps or transistors), inductors, resistors and capacitances formed in the declared generator circuit can be used commercially available from the industry. The optimal values of the parameters of the inductances, and capacitances included in the circuit for the formation of the imaginary components of the first and second complex bipolar, can be uniquely determined using mathematical expressions given in the claims.

The technical and economic efficiency of the proposed method and device consists in ensuring the generation and frequency modulation of a high-frequency signal due to the choice of circuits (Fig. 3) and parameter values of the elements L _1k , C _1k , L _0k for realizing the imaginary components of the resistances of the first and second complex two-terminal networks - 13 , 14 for the device shown in FIG. 2, according to the criterion of sequentially ensuring the conditions of the balance of phases and amplitudes in a given frequency band and in the corresponding range of simultaneous changes in the amplitude of the control signal on a non-linear three-pole element, which allows the generation of frequency-modulated signals for radio communications and electronic warfare with a greater physical realizability of the specified result.

Claims (2)

1. The method of generation and frequency modulation of high-frequency signals, based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, the interaction of a high-frequency signal with a direct transmission circuit made of a three-pole nonlinear element and a four-terminal, load and external feedback circuit, the fulfillment of the excitation conditions in the form amplitude balance and phase balance, respectively determining the amplitude and frequency of the generated high-frequency signals, matching conditions of the circuit direct transmission with the load and conditions for matching the load with the control electrode of a three-pole non-linear element, changing the frequency of the generated signal according to the law of changing the amplitude of the low-frequency control signal, characterized in that the direct transmission circuit is made of cascade-connected complex four-terminal and three-pole non-linear element, the load is performed in the form the first two-terminal with complex resistance, an arbitrary complex four is used as the external feedback circuit the x-pole connected in parallel to the direct transmission circuit, the direct-transmission circuit and the feedback circuit as a single node are cascaded between the introduced second two-terminal network with a complex resistance simulating the resistance of the signal source of the generator and the frequency modulator in amplification mode and the load, in the interest of realizing frequency modulation of the condition excitations in the form of a balance of amplitudes and phase balance and matching conditions are sequentially performed in a given frequency band and the corresponding amplitude variation range uds of the low-frequency control signal by selecting the frequency dependences of the imaginary components of the resistance of the first x _n and second x ₀ two-terminal with complex resistances from the condition of providing a stationary generation mode in the form of equality to zero of the denominator of the gain in the gain band in the given frequency band and the corresponding range of the amplitude of the low-frequency control signal in accordance with the following mathematical expressions:

Where

a ₁ = Re ( a ₀ ), a ₂ = Im ( a ₀ ), b ₁ = Re (b ₀ ), b ₂ = Im (b ₀ ), c ₁ = Re (c ₀ ), c ₂ = Im ( c ₀ ), d ₁ = Re (d ₀ ), d ₂ = Im (d ₀ ) are the frequency dependences of the real and imaginary components of the unnormalized elements of the classical transmission matrix of the entire device; a, b, c, d - given frequency dependences of the complex elements of the classical transmission matrix of a complex four-terminal network in a direct transmission circuit at given frequencies;

- the given dependences of the complex elements of the conductivity matrix of a three-pole nonlinear element in the direct transmission circuit on the frequency of the generated signal and the amplitude of the low-frequency signal;

- given frequency dependences of the complex elements of the conductivity matrix of a complex four-terminal feedback loop; r _n , r ₀ - given frequency dependencies of the real components of the complex load resistances and the resistance of the signal source of the generation device and frequency modulation in the amplification mode. 2. Device for the generation and frequency modulation of high-frequency signals, consisting of a constant voltage source and a low-frequency control signal, a direct transfer circuit of a three-pole nonlinear element and a four-terminal, load and external feedback circuit, characterized in that the direct transmission circuit is made of cascade-connected complex a four-terminal and a three-pole nonlinear element, the load is made in the form of the first two-terminal with complex resistance, as an external feedback circuit An arbitrary complex four-terminal network connected in parallel to the direct transmission circuit was used, the direct transmission circuit and the feedback circuit as a single unit are cascaded between the introduced second two-terminal network with complex resistance simulating the resistance of the signal source of the generator and the frequency modulator in amplification mode and the load, imaginary components first and second two-terminal networks with complex impedances z and z _{0n Hn} formed of serial oscillating circuit with parameters L _1k, C _1k, couple allel connected to the inductance L _0k, parameter values L _1k, C _1k, L _0k to ensure frequency modulation determined from the conditions for the realization of a stationary lasing in a vanishing denominator coefficient mode gain at three predetermined frequencies and respective three values of low frequency control of the amplitude signal in accordance with the following mathematical expressions:

Where

ω _n = 2πf _n ; f _n - given frequencies; n = 1, 2, 3 - numbers of the given frequencies; k = 0, n is the index characterizing the resistance of the signal source of the generator and the frequency modulator in the amplification mode (k = 0) and load (k = n), respectively; a ₁ = Re ( a ₀ ), a ₂ = Im ( a ₀ ), b ₁ = Re (b ₀ ), b ₂ = Im (b ₀ ), c ₁ = Re (c ₀ ), c ₂ = Im ( _in c), d ₁ = Re (d _0), d ₂ = Im (d ₀₎ - real and imaginary components of the unnormalized transmit matrix elements of classical whole device; a _n , b _n , c _n , d _n - given values of the complex elements of the classical transmission matrix of a complex four-terminal network in a direct transmission circuit at given frequencies;

- setpoints of the complex elements of the conductivity matrix of a three-pole nonlinear element in the direct transmission circuit at the given frequencies and the corresponding three values of the amplitude of the low-frequency control signal;

- setpoints of the complex elements of the conductivity matrix of a complex quadrupole feedback circuit at given frequencies; r _nn , r _0n - set values of the real components of the complex load resistances and the resistance of the signal source of the device for generating and frequency modulation in the amplification mode at given frequencies.

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