RU2500066C2 - Method for generation and frequency-modulation of high-frequency signals and apparatus for realising said method - Google Patents

Abstract

FIELD: radio engineering, communication.

SUBSTANCE: apparatus for generation and frequency modulation of high-frequency signals consists of a source of dc voltage and a low-frequency control signal, a three-terminal nonlinear element, a forward transmission circuit, a feedback circuit and a load, wherein the forward transmission circuit consists of a three-terminal nonlinear element; the feedback circuit used is an external feedback in form of an arbitrary four-terminal element connected to the three-terminal nonlinear element on a series-parallel circuit; the three-terminal nonlinear element is connected by the output electrode and common electrode to the load, which is in form of a first two-terminal element with complex resistance; the control electrode and the common electrode of the three-terminal nonlinear element is connected to a second two-terminal element with complex resistance; the imaginary component of the load resistance and the imaginary component of the resistance of the source of the input high-frequency signal of the generator and the frequency modulator in gain mode are composed of two series-connected parallel circuits with parameters.

EFFECT: high noise-immunity of the receiver.

2 cl, 3 dwg

Description

The invention relates to the fields of radio communications, radar, radio navigation and electronic warfare and can be used to create compact devices for generating and frequency modulation with an increased linear portion of the frequency modulation characteristic.

A known method of generating and frequency modulating a high-frequency signal, based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, organizing internal feedback in the first non-linear element by using a bipolar non-linear element with negative differential resistance as it, fulfilling the excitation conditions in the form of a balance of amplitudes and phase balance, respectively determining the amplitude and frequency of the generated high-frequency signal, and s approval of the first non-linear element to the load, changing the frequency of the high frequency signal generated by changing the phase balance by changing the parameter of the second non-linear element included in the selective loading according to the law of change of amplitude of low-frequency control (primary, informational) signals [IS Gonorovsky Radio circuits and signals. - M .: “Bustard”, 2006, p. 414-417, 434-437].

A device for generating and frequency modulating a high-frequency signal, consisting of a constant voltage source that sets the operating point in the middle of the falling section of the current-voltage characteristic of a bipolar nonlinear element with negative differential resistance, a four-terminal reactive load, in the form of a parallel oscillatory circuit with a varicap connected to the control signal source , while the parameters of the circuit, bipolar nonlinear element and varicap selected anes conditions of maintenance of the set amplitude and frequency change range generated by the high frequency signal by the low frequency control law of the amplitude change (primary, informational) signals [IS Gonorovsky Radio circuits and signals. - M .: “Bustard”, 2006, p. 414-417, 434-437].

The principle of operation of this device is as follows. When a constant voltage (current) source is turned on, due to an abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of internal feedback in a bipolar nonlinear element, a negative differential resistance arises in the section with a falling current-voltage characteristic, which, by matching with a reactive four-terminal, compensates for losses in the circuit. Due to this, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is amplified until the amplitude of this oscillation increases to a level at which the amplitude goes beyond the falling section of the current-voltage characteristic. There is a stationary mode. In this mode, a change in the capacitance of a varicap under the action of a control signal leads to a change in the frequency of the generated signal according to the law of change in the amplitude of the low-frequency signal.

The disadvantage of this method and device is the presence of two non-linear elements, one of which works as an amplifier and limiter, and the second is used to change the frequency of the generated high-frequency signal.

The closest in technical essence and the achieved result (prototype) is a method for generating and frequency modulating a high-frequency signal, based on converting the energy of a constant voltage source into energy of a high-frequency signal, building a direct transfer circuit between the output electrode of a three-pole nonlinear element and the load, organizing external positive feedback between the load and the control electrode of a three-pole nonlinear element, the fulfillment of the excitation conditions in the form of ba the amplitude balance and the phase balance, which respectively determine the amplitude and frequency of the generated high-frequency signal, and the conditions for matching the three-pole nonlinear element with the load, change the frequency of the generated high-frequency signal by changing the phase balance by changing the parameter of the two-pole nonlinear element included in the selective load, according to the law of amplitude change low-frequency control (primary, informational) signal [Gonorovsky I.S. Radio circuits and signals. - M .: “Bustard”, 2006, p. 434-437].

The closest in technical essence and the achieved result (prototype) is a device for generating and frequency modulating a high-frequency signal, consisting of a constant voltage source that sets an operating point in the middle of the quasilinear section of the transient current-voltage characteristic of the transistor, a direct transmission circuit in the form of a first four-terminal device for matching the output transistor electrode and loads, loads in the form of a parallel oscillatory circuit, which includes a varicap connected to the source of the control signal, the RC circuit of the external positive feedback (in general, the second four-terminal network for matching the control electrode of the transistor and the load) between the load and the control electrode of the transistor, while the parameters of the circuit, forward circuit, feedback circuit, transistor and varicap are selected from the condition of providing the given amplitude and frequency range of the generated high-frequency signal according to the law of changing the amplitude of the low-frequency control (primary, information) Igna [Gonorovsky IS Radio circuits and signals. - M .: “Bustard”, 2006, p. 434-437].

The principle of operation of this device is as follows. When a constant voltage (current) source is turned on, due to an abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of an external positive feedback circuit, the oscillation with a frequency equal to the resonant frequency of the oscillating circuit is supplied to the control electrode of the transistor, which, by virtue of matching with the help of two four-terminal devices, starts to operate in the amplification mode until the amplitude of this oscillation increases to a level at which saturation mode occurs (amplitude limits). There is a stationary mode. In this mode, a change in the capacitance of a varicap under the action of a control signal leads to a change in the frequency of the generated signal according to the law of change in the amplitude of the low-frequency signal.

The disadvantages of this method and device are the need to use two nonlinear elements (one to enhance and limit the amplitude, the second to change the frequency) and a small linear section of the modulation characteristic due to the smallness of the linear section of the capacitance-voltage characteristic of the varicap. In addition, it does not indicate how it is necessary to choose the values of the parameters of both four-terminal networks, at which the excitation mode and the stationary mode occur. This question arises especially sharply when designing generation and frequency modulation devices in the HF and UHF bands, on which the reactive components of the parameters of nonlinear elements must be taken into account. Currently, the classical theory of radio circuits does not take this into account. In addition, frequency modulation can be achieved without a four-terminal network, which leads to a decrease in the number of reactive elements, that is, to a decrease in mass and dimensions.

The technical result of the invention is the generation and frequency modulation of a high-frequency signal with an increased linear portion of the frequency modulation characteristic using a single nonlinear element, which allows creating efficient compact devices for generating and frequency modulation, as well as increasing the range of generated oscillations when using a reactive basis with lumped parameters. The use of various types of feedback expands the possibilities of physical feasibility of the specified result.

1. The specified result is achieved by the fact that in the known method of generating and frequency modulating a high-frequency signal, based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, the interaction of a high-frequency signal with a direct transmission circuit, a three-pole nonlinear element, a feedback circuit and a load, the conditions excitations in the form of a balance of amplitudes and a balance of phases, which respectively determine the amplitude and frequency of the generated high-frequency signal, and the conditions of agreement of a three-pole nonlinear element with a load, a change in the frequency of the generated high-frequency signal according to the law of changing the amplitude of the low-frequency control signal by a corresponding change in the phase balance, in addition, the direct transfer circuit is made of a three-pole nonlinear element, external feedback in the form of an arbitrary four-pole connected as a feedback circuit is used with a three-pole nonlinear element in a series-parallel circuit, change the frequency of the generated about a high-frequency signal and implement matching conditions by changing the amplitude of the control signal on a three-pole nonlinear element connected to the output and common electrodes to a load made in the form of the first two-terminal with complex resistance, connect the second two-terminal with complex resistance to the control and common electrodes of the three-pole nonlinear element, simulating the resistance of the signal source of the generator and the frequency modulator in amplification mode, the excitation conditions in the form of a balance and the amplitudes and phase balance and matching conditions are fulfilled by selecting the dependences of the imaginary components of the first x _n and second x ₀ two-terminal resistances on the frequency from the condition of providing a stationary generation mode in the form of equal to zero denominator of the gain in gain mode sequentially over the entire specified range of frequency changes generated high-frequency signals according to the law of the amplitude of the low-frequency control signal in accordance with the following mathematical expressions:

dependences of the real component and optimal dependences of the imaginary component of the resistance of the source of the input high-frequency signal of the generator and the frequency modulator in the amplification mode on the frequency in a given frequency band; r _n , x _n - the given dependences of the real component and the optimal dependence of the imaginary component of the load resistance on the frequency in a given frequency band; r ₁₁ , x ₁₁ , r ₁₂ , x ₁₂ , r ₂₁ , x ₂₁ , r ₂₂ , x ₂₂ - given dependences of the total real and imaginary components of the elements of the mixed matrix H of the three-pole nonlinear element and the mixed matrix n of the feedback circuit h ₁₁ = r ₁₁ + jx ₁₁ , h ₁₂ = r ₁₂ + jx ₁₂ , h ₂₁ = r ₂₁ + jx ₂₁ , h ₂₂ = r ₂₂ + jx ₂₂ of the frequency in a given frequency band with a corresponding change in the amplitude of the low-frequency control signal.

2. This result is achieved by the fact that in the device for generating and frequency modulating high-frequency signals, consisting of a constant voltage source and a low-frequency control signal, a three-pole nonlinear element, a direct transmission circuit, a feedback circuit and a load, additionally, the direct transmission circuit is made of a three-pole nonlinear element , external feedback in the form of an arbitrary four-terminal connected to a three-pole nonlinear element via In an ice-parallel circuit, a three-pole non-linear element with the output and common electrodes is connected to a load made in the form of the first two-terminal with complex resistance, a second two-terminal with complex resistance, which simulates the resistance of the source of the input high-frequency signal of the generator and the frequency, is connected to the control and common electrodes of the three-pole non-linear element modulator in gain mode, the imaginary component of the load resistance and the imaginary component of the source resistance The high-frequency input signal of the generator and the frequency modulator in amplification mode are implemented from two parallel-connected parallel loops with parameters L _1k , C _1k , L _2k , C _2k , and the parameter values are determined from the condition of providing a stationary generation mode at four frequencies of a given frequency band and corresponding four values of the amplitude of the low-frequency control signal using the following mathematical expressions:

the input high-frequency signal of the generator and the frequency modulator in the gain and load mode at the given four frequencies ω _m = 2πf _m ; m = 1, 2, 3, 4 - frequency number; r _0m - set values of the real component of the resistance of the source of the input high-frequency signal of the generator in the amplification mode at four frequencies; r _nm - set values of the real component of the load resistance at four frequencies; r _11n , x _11m , r _12m , x _12m , r _21m , x _21m , r _22m , x _22m are the given values of the total real and imaginary components of the elements of the mixed matrix H of a three-pole nonlinear element and the mixed matrix H of the feedback circuit h _11m = r _11m + jx _11m , h _12m = r _12m + jx _12m , h _21m = r _21m + jx _21m , h _22m = r _22m + jx _22m at given four frequencies and corresponding four values of the amplitude of the low-frequency control signal; k = 0, n is the index characterizing the imaginary components of the load resistance and the signal source in the amplification mode.

Figure 1 shows a diagram of a device for generating and frequency modulating high-frequency signals (prototype) that implements the prototype method.

Figure 2 shows the structural diagram of the proposed device according to claim 2., Which implements the proposed method of generation and frequency modulation according to claim 1 in the amplification mode.

Figure 3 shows a diagram of a reactive two-terminal network that implements the imaginary component of the complex resistance of the generator signal source in the gain and load mode.

The prototype device (Figure 1), which implements the prototype method, contains a direct transmission circuit in the form of a three-pole non-linear element VT-1 connected to a constant voltage source-2, the first matching filtering device SFU-3 (the first reactive four-terminal or the first matching four-terminal) and loads in the form of an oscillatory circuit on the elements L - 4, R - 5, C (t) - 6. The first SFU-3 is connected between the output electrode of the three-pole nonlinear element and the load. The controlled capacitance C (t), implemented by the varicap — 6, is connected to the source of the low-frequency control (information) signal — 7. Between the load and the control electrode of the three-pole nonlinear element, the second SFU-9 (second reactive four-terminal or second matching four-terminal) is connected with it the input of the first two-terminal - 8 and the output of the second two-terminal - 10 with complex resistances in the transverse circuits. All this together forms an external feedback circuit. The first two-terminal - 8 is connected to the load. The second two-terminal - 10 is connected to the control electrode of a three-pole nonlinear element.

The principle of operation of the device for generating and modulating high-frequency signals (prototype) that implements the prototype method is as follows.

When you turn on the DC voltage source - 2 due to the abrupt change in the amplitude in the entire circuit, oscillations occur, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of external feedback, matching with the first reactive four-terminal device - 3 output electrodes of a three-pole nonlinear element and load (direct transfer circuit), matching with a feedback circuit (first two-terminal device - 8 with complex resistance, second reactive four-terminal device - 9 and the second bipolar - 10 with complex resistance) of the load and the control electrode of a three-pole nonlinear element compensates for losses in the circuit L - 4, R - 5, C (t) - 6. Due to this, the reverse I the connection becomes positive and the conditions of phase balance and amplitudes are realized - the conditions for the excitation of electromagnetic oscillations. As a result, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is supplied to the control electrode of a three-pole nonlinear element, which at the initial stage operates in amplification mode. The amplitude of this oscillation is amplified until it increases to a level at which the limiting state of a three-pole nonlinear element occurs. The stationary mode of generation sets in. In this mode, a change in the capacitance of the varicap C (t) - 6 under the action of the control signal of the source-7 leads to a change in the frequency of the generated signal according to the law of the amplitude of this signal.

The disadvantages of the prototype method and device for its implementation are described above. The proposed device according to claim 2 (figure 2), which implements the proposed method according to claim 1, contains a three-pole non-linear element-1 with known elements of a mixed matrix H

$$h_{\mathrm{eleven}m}^{VT}=r_{\mathrm{eleven}m}^{VT}+j{x}_{\mathrm{eleven}m}^{VT},$$

$$h_{12m}^{VT}=r_{12m}^{VT}+j{x}_{12m}^{VT},$$

$$h_{21m}^{VT}=r_{21m}^{VT}+j{x}_{21m}^{VT},$$

$$h_{22m}^{VT}=r_{22m}^{VT}+j{x}_{22m}^{VT}$$

at given frequencies of generated signals, connected to a source of constant voltage and low-frequency control signal - 13 and cascaded at a high frequency between the source of the input high-frequency signal in gain mode with resistance z _0m = r _0m + jx _0m - 12 at given frequencies, simulating the source resistance of high-frequency oscillations that occur when the DC voltage source is turned on - 13 at the time of an abrupt change in the amplitude of its voltage in the generation mode, and by a load of 11 with resistances z _nm = r _nm + jx _nm at given frequencies. In addition, a three-pole non-linear element-1 in a parallel-parallel circuit (inputs are connected in series and outputs are connected in parallel) is connected to an external feedback circuit in the form of an arbitrary four-terminal - 14 with known elements of a mixed matrix H

$$h_{12m}^{OC}=r_{12m}^{OC}+j{x}_{12m}^{OC},$$

$$h_{21m}^{OC}=r_{21m}^{OC}+j{x}_{21m}^{OC},$$

$$h_{22m}^{OC}=r_{22m}^{OC}+j{x}_{22m}^{OC}.$$

Синтез генератора (выбор значений мнимых составляющих сопротивлений источника входного высокочастотного сигнала генератора в режиме усиления и нагрузки на четырех заданных частотах (m=1, 2, 3, 4 - номер частоты), схем формирования этих двухполюсников (фиг.3) осуществлен по критерию обеспечения баланса амплитуд и баланса фаз путем реализации равенства нулю знаменателя коэффициента передачи устройства генерации в режиме усиления последовательно на заданных частотах генерируемых сигналов при соответствующих четырех значениях амплитуды низкочастотного управляющего сигнала. В режиме генерации источник входного высокочастотного сигнала отключается и вместо него устанавливается короткозамыкающая перемычка. $$h_{\mathrm{eleven}m}^{OC}=r_{\mathrm{eleven}m}^{OC}+j{x}_{\mathrm{eleven}m}^{OC},$$

$$h_{12m}^{OC}=r_{12m}^{OC}+j{x}_{12m}^{OC},$$

$$h_{21m}^{OC}=r_{21m}^{OC}+j{x}_{21m}^{OC},$$

$$h_{22m}^{OC}=r_{22m}^{OC}+j{x}_{22m}^{OC}.$$

The synthesis of the generator (the choice of the values of the imaginary components of the resistance of the source of the input high-frequency signal of the generator in the gain and load mode at four preset frequencies (m = 1, 2, 3, 4 is the frequency number), the circuits for the formation of these two-terminal devices (Fig. 3) are carried out according to the criterion of ensuring balance of amplitudes and phase balance by implementing the vanishing of the denominator of the transmission coefficient of the generation device in the amplification mode sequentially at the given frequencies of the generated signals at the corresponding four values of the amplitude of the bottom ochastotnogo control signal. The power generation mode input high-frequency signal is turned off and instead, a shorting jumper is installed.

The proposed device operates as follows.

When you turn on the DC voltage source - 13 due to the abrupt change in the amplitude in the entire circuit, oscillations arise, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of the four-terminal - 14 in the circuit, external feedback arises, which, due to the indicated choice of the values of the imaginary components of the resistance of the source of the input high-frequency signal of the generator in the amplification mode - 12 and load - 11, becomes positive and ensures the fulfillment of the conditions of amplitude balance and phase balance, which is equivalent to the occurrence of negative resistance, which compensates for losses in the entire circuit simultaneously at four given frequencies. The oscillation amplitudes with given frequencies are amplified to certain levels and then limited. Due to this, the oscillations with the given four frequencies are amplified until the amplitudes of these oscillations increase to a level at which the amplitude goes beyond the quasilinear section of the current-voltage characteristic of the passage. There is a stationary mode. With a reasonable choice of the positions of the four frequencies relative to each other, a change in the elements of the mixed matrix of a nonlinear element under the action of a control signal in this mode leads to a change in the frequency of the generated signal according to the law of the amplitude of the control signal in a larger frequency band and a wider range of the amplitude of the low-frequency signal, that is, it increases the quasilinear plot frequency modulation characteristics.

, $$h_{12}^{VT}=r_{12}^{VT}+j{x}_{12}^{VT},$$

$$h_{21}^{VT}=r_{21}^{VT}+j{x}_{21}^{VT}$$

, $$h_{22}^{VT}=r_{22}^{VT}+j{x}_{22}^{VT}$$

и цепи обратной связи $$h_{11}^{OC}=r_{11}^{OC}+j{x}_{11}^{OC}$$

, $$h_{12}^{OC}=r_{12}^{OC}+j{x}_{12}^{OC},$$

$$h_{21}^{OC}=r_{21}^{OC}+j{x}_{21}^{OC}$$

, $$h_{22}^{OC}=r_{22}^{OC}+j{x}_{22}^{OC}$$

, от частоты, которые можно определить по известным (например, измеренным или рассчитанным) элементам матриц сопротивлений, проводимостей или передачи. При последовательно-параллельном соединении четырехполюсников элементы их смешанных матриц H складываются. Суммарные зависимости элементов матриц H цепи прямой передачи в виде нелинейного элемента и цепи обратной связи от частоты: h₁₁=r₁₁+jx₁₁, h₁₂=r₁₂+jx₁₂, h₂₁=r₂₁+jx₂₁, h₂₂=r₂₂+jx₂₂. Размерности элементов матрицы H: h₁₁ (проводимость), h₁₂ (безразмерный), h₂₁ (безразмерный), h₂₂ (сопротивление).Let us prove the feasibility of implementing these properties. Let us introduce the designations of the given dependences of the resistance of the signal source in the amplification mode z ₀ = r ₀ + jx ₀ and the load z _n = r _n + jx _n on frequency. The initial ones are also the dependences of the elements of the mixed matrix H of a three-pole nonlinear element $$h_{\mathrm{eleven}}^{VT}=r_{\mathrm{eleven}}^{VT}+j{x}_{\mathrm{eleven}}^{VT}$$

, $$h_{12}^{VT}=r_{12}^{VT}+j{x}_{12}^{VT},$$

$$h_{21}^{VT}=r_{21}^{VT}+j{x}_{21}^{VT}$$

, $$h_{22}^{VT}=r_{22}^{VT}+j{x}_{22}^{VT}$$

and feedback circuits $$h_{\mathrm{eleven}}^{OC}=r_{\mathrm{eleven}}^{OC}+j{x}_{\mathrm{eleven}}^{OC}$$

, $$h_{12}^{OC}=r_{12}^{OC}+j{x}_{12}^{OC},$$

$$h_{21}^{OC}=r_{21}^{OC}+j{x}_{21}^{OC}$$

, $$h_{22}^{OC}=r_{22}^{OC}+j{x}_{22}^{OC}$$

, from the frequency, which can be determined by the known (for example, measured or calculated) elements of the matrices of resistance, conductivity or transmission. With a series-parallel connection of the four-terminal devices, the elements of their mixed matrices H are added. The total dependences of the matrix elements H of the direct transmission circuit in the form of a nonlinear element and feedback loop on frequency: h ₁₁ = r ₁₁ + jx ₁₁ , h ₁₂ = r ₁₂ + jx ₁₂ , h ₂₁ = r ₂₁ + jx ₂₁ , h ₂₂ = r ₂₂ + jx ₂₂ . The dimensions of the elements of the matrix H: h ₁₁ (conductivity), h ₁₂ (dimensionless), h ₂₁ (dimensionless), h ₂₂ (resistance).

The general mixed matrix H of the nonlinear element (VT) and the four-terminal feedback loop (OS) and the corresponding classical transmission matrix of the entire device, taking into account normalization conditions:

$$H=\left|\begin{array}{cc}{h}_{\mathrm{eleven}}& h_{12}\\ h_{21}& h_{22}\end{array}\right|;A=\left|\begin{array}{cc}\frac{-\left|h\right|}{h_{21}}\sqrt{\frac{z_n}{z_0}}& \frac{h_{\mathrm{eleven}}}{h_{21}}\frac{\mathrm{one}}{\sqrt{z_0{z}_n}}\\ \frac{-h_{22}}{h_{21}}\text{A.}\sqrt{z_0{z}_n}& \frac{\mathrm{one}}{h_{21}}\sqrt{\frac{z_0}{z_n}}\end{array}\right|,\left(\mathrm{one}\right)$$

where | h | = h ₁₁ h ₂₂ -h ₁₂ h ₂₁ .

Using the well-known connection between the elements of the scattering matrix and the elements of the classical transmission matrix (Feldstein A.L., Yavich L.R. Synthesis of four-terminal and eight-terminal devices on microwave. M: Communication, 1971, p. 34-36) and the transmission matrix from (1) , we obtain the expression for the gain of the generator in amplification mode:

$$S_{21}=\frac{2h_{21}\sqrt{z_0{z}_n}}{z_0+h_{\mathrm{eleven}}-z_n\left(z_0{h}_{22}+\left|h\right|\right)}.\left(2\right)$$

,We transform the denominator of the transmission coefficient and write it in the form corresponding to the condition for the emergence of a stationary generation mode $$\mathrm{one}-\frac{z_n\left|h\right|-h_{\mathrm{eleven}}}{\left(\mathrm{one}-h_{22}{z}_n\right)z_0}=0$$

,

or the condition for the balance of amplitudes and phase balance 1-KV = 0 (Gonorovsky IS Radio engineering circuits and signals. - M .: "Bustard", - 2006, p. 383) for a circuit with external positive feedback. For this type of generator and frequency modulator

$$K=\frac{z_n{h}_{21}}{\left(\mathrm{one}-h_{22}{z}_n\right)z_0}$$

- gear ratio of the direct transmission circuit;

$$B=\frac{z_n\left|h\right|-h_{\mathrm{eleven}}}{\left(\mathrm{one}-h_{22}{z}_n\right)z_0}$$

- feedback loop gain.

There are other possible representations of the values of K and B. This difference is not of fundamental importance for the invention. In any case, the conditions for the balance of amplitudes and phase balance correspond to the equality to zero of the denominator of the transfer coefficient.

We equate the denominator of the transmission coefficient to zero and divide the real and imaginary parts. We get a system of two algebraic equations:

The implementation of the optimal approximating functions (4) can be carried out in various ways, for example, using the interpolation method by finding the values of the parameters of the selected reactive two-terminal networks at which their resistances at the given frequencies coincide with the optimal ones. Let the imaginary component chi of the load resistance and the imaginary component ^ of the resistance of the source of the input high-frequency signal of the generator and the frequency modulator in the amplification mode be formed from two parallel-connected parallel circuits L _1k , C _1k , L _2k , C _2k = (k = 0, n - (Fig .3)). For N = 4, we compose two systems of four equations:

The implementation of optimal approximations of the frequency characteristics (4) using (6) provides an increase in the frequency range of the generated signal, since it implements the condition of amplitude balance and phase balance at four frequencies of a given modulation characteristic or a given frequency range for the corresponding four values of the amplitude of the control signal. This allows for a reasonable choice of the positions of the given frequencies relative to each other ω ₁ -ω ₂ , ω ₁ -ω ₃ , ω ₁ -ω ₄ , ω ₂ -ω ₃ , ω ₂ -ω ₄ , ω ₃ -ω ₄ to expand the linear section of the modulation characteristics.

The proposed technical solutions have an inventive step, since it does not explicitly follow from published scientific data and known technical solutions that the claimed sequence of operations (switching on a three-pole nonlinear element between the input resistance of the generator high-frequency signal source in amplification mode and the load, as well as in serial-parallel circuit with an external feedback circuit in the form of an arbitrary four-terminal network (figure 2), the choice of frequency characteristics of the imaginary component the resistance of the source of the high-frequency signal of the generator in the amplification mode and the imaginary component of the load resistance, the formation of their circuits in the indicated form (Fig. 3), the choice of the values of their parameters from the condition of providing a stationary generation mode at four frequencies and the corresponding four values of the amplitude of the low-frequency control signal on non-linear three-pole element), leads to a change in the frequency of the generated signal according to the law of change in the amplitude of the control signal in a larger frequency band and a larger a range of changes in the amplitude of the low-frequency signal, that is, it increases the quasilinear section of the frequency modulation characteristic.

The proposed technical solutions are practically applicable, since for their implementation three-pole non-linear elements (transistors or lamps) commercially available by the industry, reactive elements formed in the declared schemes of reactive two-pole can be used (FIG. 3). The values of the parameters of the inductances and capacitances of these circuits can be uniquely determined using mathematical expressions given in the claims.

The technical and economic efficiency of the proposed device consists in sequentially generating a high-frequency signal at four predetermined frequencies and corresponding four values of the amplitude of the control signal by choosing a circuit and values of the parameters of the reactive elements according to the criterion of ensuring the conditions of phase balance and amplitudes at these frequencies with a variable state of a three-pole nonlinear element , which in dynamics leads to a change in the frequency of the generated signal according to the law of change in the amplitude of control vlyayuschego signal in the frequency band greater and greater range of variation of the low frequency signal amplitude, i.e. quasi-linear portion increases the frequency modulation characteristic with a minimum number of circuit elements.

Claims (2)

1. A method for generating and frequency modulating a high-frequency signal, based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, the interaction of a high-frequency signal with a direct transmission circuit, a three-pole nonlinear element, a feedback circuit and a load, fulfilling the excitation conditions in the form of amplitude balance and phase balance , which respectively determine the amplitude and frequency of the generated high-frequency signal, and the conditions for matching a three-pole nonlinear element with a load th, changing the frequency of the generated high-frequency signal according to the law of changing the amplitude of the low-frequency control signal by correspondingly changing the phase balance, characterized in that the direct transfer circuit is made of a three-pole nonlinear element, external feedback in the form of an arbitrary four-terminal connected to a three-pole is used as a feedback circuit nonlinear element in a series-parallel circuit, change the frequency of the generated high-frequency signal and implement the conditions coordination by changing the amplitude of the control signal on a three-pole non-linear element connected by the output and common electrodes to the load, made in the form of the first two-terminal with complex resistance, to the control and common electrodes of the three-pole non-linear element connect a second two-terminal with complex resistance, simulating the resistance of the generator signal source and frequency modulator in gain mode, excitation conditions in the form of a balance of amplitudes and phase balance and matching conditions they are performed by choosing the dependences of the imaginary components of the resistance of the first x _n and second x ₀ two-terminal on frequency from the condition of providing a stationary generation mode in the form of equal to zero the denominator of the transmission coefficient in the gain mode sequentially over the entire specified frequency range of the generated high-frequency signals according to the law of the amplitude of the low-frequency control signal in accordance with the following mathematical expressions:
$$x_0=\frac{A{x}_n+B}{C{x}_n+D};$$

$$x_n=\frac{-Y\pm \sqrt{Y^2-\mathrm{four}XZ}}{2X},$$

where where A = - (x ₂₂ r ₀ + B ₁ ); B = r _n (A ₁ + r ₀ r ₂₂ ) -r ₀ -r ₁₁ ; C = r ₂₂ ; D = x ₂₂ r _n ; X = -r ₂₂ (r ₂₂ r ₀ + A ₁ ); Y = r ₂₂ r ₁₁ -B ₁ -x ₂₂ (r ₂₂ r ₀ r _n + r ₀ + A ₁ r _n );
$$Z=r_n(r_{\mathrm{eleven}}{r}_{12}+x_{\mathrm{eleven}}{x}_{22})-r_0{r}_n^2(r_{22}^2+x_{22}^2)-r_n^2(A_{\mathrm{one}}{r}_{22}+B_{\mathrm{one}}{x}_{22})-r_{\mathrm{eleven}}-r_0+2r_0{r}_n{r}_{22}+A_{\mathrm{one}}{r}_n;$$

A ₁ = r ₁₁ r ₂₂ -x ₁₁ x ₂₂ -r ₁₂ r ₂₁ + x ₁₂ x ₂₁ ; B ₁ = x ₁₁ r ₂₂ + r ₁₁ x ₂₂ -x ₁₂ r ₂₁ -r ₁₂ x ₂₁ ; r ₀ , x ₀ are the given dependences of the real component and the optimal dependences of the imaginary component of the resistance of the source of the input high-frequency signal of the generator and the frequency modulator in the amplification mode on the frequency in a given frequency band; r _n , x _n - the given dependences of the real component and the optimal dependence of the imaginary component of the load resistance on the frequency in a given frequency band; r ₁₁ , x ₁₁ , r ₁₂ , x ₁₂ , r ₂₁ , x ₂₁ , r ₂₂ , x ₂₂ are the given dependences of the total real and imaginary components of the elements of the mixed matrix H of the three-pole nonlinear element and the mixed matrix H of the feedback circuit h ₁₁ = r ₁₁ + jx ₁₁ , h ₁₂ = r ₁₂ + jx ₁₂ , h ₂₁ = r ₂₁ + jx ₂₁ , h ₂₂ = r ₂₂ + jx ₂₂ of the frequency in a given frequency band with a corresponding change in the amplitude of the low-frequency control signal. 2. A device for generating and frequency modulating high-frequency signals, consisting of a constant voltage source and a low-frequency control signal, a three-pole nonlinear element, a direct transmission circuit, a feedback circuit and a load, characterized in that the direct transmission circuit is made of a three-pole nonlinear element, as a circuit feedback, external feedback in the form of an arbitrary four-terminal connected to a three-pole nonlinear element in a series-parallel circuit, tr an ex-pole nonlinear element with the output and common electrodes is connected to a load made in the form of the first two-terminal with complex resistance, a second two-terminal with complex resistance, which simulates the resistance of the source of the input high-frequency signal of the generator and the frequency modulator in the amplification mode, is connected to the control and common electrodes of the three-pole non-linear element the imaginary component of the load resistance and the imaginary component of the resistance of the source of the input high-frequency signal ala generator and frequency modulator in an amplification regime realized from two series-connected parallel circuit with parameters _{L 1k, C 1k, L 2k} , C 2k, wherein the parameter values are determined from the condition of ensuring steady state lasing at four frequencies of a predetermined frequency band and the respective four values of amplitude low-frequency control signal using the following mathematical expressions:
$$L_{\mathrm{one}k}=\frac{e_{\mathrm{one}}{x}_{k2}+h_{\mathrm{one}}{x}_{k\mathrm{one}}}{{\omega }_{\mathrm{one}}{\omega }_2({\omega }_{\mathrm{one}}^2-{\omega }_2^2)\left(B-A\right)};$$

$$L_{2k}=\frac{e_2{x}_{k2}+h_2{x}_{k\mathrm{one}}}{{\omega }_{\mathrm{one}}{\omega }_2({\omega }_{\mathrm{one}}^2-{\omega }_2^2)\left(B-A\right)};$$

$$C_{\mathrm{one}k}=\frac{A}{L_{\mathrm{one}k}};$$

$$C_{2k}=\frac{B}{L_{2k}},$$

Where $$B=\frac{-\gamma \pm \sqrt{y^2-\mathrm{four}xz}}{2x};$$

$$A=\frac{a_{\mathrm{one}}B+b_{\mathrm{one}}}{c_{\mathrm{one}}B+d_{\mathrm{one}}}=\frac{a_{2}B+b_2}{c_{2}B+d_2};$$

x = a ₂ s ₁ - a ₁ s ₂ ; y = a ₂ d ₁ + b ₂ c ₁ - a ₁ d ₂ -b ₁ c ₂ ; z = b ₂ d ₁ -b ₁ d ₂ ;
$$e_{\mathrm{one}}={\omega }_{\mathrm{one}}(\mathrm{one}-{\omega }_2^{2}B)\left(\mathrm{one}+A^2{\omega }_{\mathrm{one}}^2{\omega }_2^2-A\left({\omega }_{\mathrm{one}}^2+{\omega }_2^2\right)\right)$$

; $$h_{\mathrm{one}}=-{\omega }_2\left(\mathrm{one}-{\omega }_{\mathrm{one}}^{2}B\right)\left(\mathrm{one}+A^2{\omega }_{\mathrm{one}}^2{\omega }_2^2-A\left({\omega }_{\mathrm{one}}^2+{\omega }_2^2\right)\right)$$

;
$$e_2=-{\omega }_{\mathrm{one}}(\mathrm{one}-{\omega }_2^{2}A)\left(\mathrm{one}+B^2{\omega }_{\mathrm{one}}^2{\omega }_2^2-B\left({\omega }_{\mathrm{one}}^2+{\omega }_2^2\right)\right);$$

$$h_2={\omega }_2\left(\mathrm{one}-{\omega }_{\mathrm{one}}^{2}A\right)\left(\mathrm{one}+B^2{\omega }_{\mathrm{one}}^2{\omega }_2^2-B\left({\omega }_{\mathrm{one}}^2+{\omega }_2^2\right)\right);$$

$$a_{\mathrm{one}}={\omega }_{\mathrm{one}}{\omega }_2{\omega }_{\mathrm{four}}^2{x}_{k\mathrm{four}}\left({\omega }_2^2-{\omega }_{\mathrm{one}}^2\right)+{\omega }_{\mathrm{one}}{\omega }_2^2{\omega }_{\mathrm{four}}{x}_{k\mathrm{four}}\left({\omega }_{\mathrm{one}}^2-{\omega }_{\mathrm{four}}^2\right)+{\omega }_{\mathrm{one}}^2{\omega }_2{\omega }_{\mathrm{four}}{x}_{k\mathrm{one}}\left({\omega }_{\mathrm{four}}^2-{\omega }_2^2\right)$$

;
$$b_{\mathrm{one}}={\omega }_{\mathrm{one}}{\omega }_2{x}_{k\mathrm{four}}\left({\omega }_{\mathrm{one}}^2-{\omega }_2^2\right)+{\omega }_{\mathrm{one}}{\omega }_{\mathrm{four}}{x}_{k2}\left({\omega }_2^2-{\omega }_{\mathrm{one}}^2\right)+{\omega }_2{\omega }_{\mathrm{four}}{x}_{k\mathrm{one}}\left({\omega }_2^2-{\omega }_{\mathrm{four}}^2\right)$$

;
$$c_{\mathrm{one}}=\left[{\omega }_{\mathrm{four}}^3{x}_{k\mathrm{four}}\left({\omega }_2^2-{\omega }_{\mathrm{one}}^2\right)+{\omega }_2^3{x}_{k2}\left({\omega }_{\mathrm{one}}^2-{\omega }_{\mathrm{four}}^2\right)+{\omega }_{\mathrm{one}}^3{x}_{k\mathrm{one}}\left({\omega }_{\mathrm{four}}^2-{\omega }_2^2\right)\right]{\omega }_{\mathrm{one}}{\omega }_2{\omega }_{\mathrm{four}};$$

$$d_{\mathrm{one}}=\left[{\omega }_{\mathrm{four}}^{}{x}_{k\mathrm{four}}\left({\omega }_{\mathrm{one}}^2-{\omega }_2^2\right)+{\omega }_2^{}{x}_{k2}\left({\omega }_{\mathrm{four}}^2-{\omega }_{\mathrm{one}}^2\right)+{\omega }_{\mathrm{one}}^{}{x}_{k\mathrm{one}}\left({\omega }_2^2-{\omega }_{\mathrm{four}}^2\right)\right]{\omega }_{\mathrm{one}}{\omega }_2{\omega }_{\mathrm{four}};$$

$$a_2={\omega }_{\mathrm{one}}{\omega }_2{\omega }_3^2{x}_{k3}\left({\omega }_2^2-{\omega }_{\mathrm{one}}^2\right)+{\omega }_{\mathrm{one}}{\omega }_2^2{\omega }_3{x}_{k2}\left({\omega }_{\mathrm{one}}^2-{\omega }_3^2\right)+{\omega }_{\mathrm{one}}^2{\omega }_2{\omega }_3{x}_{k\mathrm{one}}\left({\omega }_3^2-{\omega }_2^2\right)$$

;
$$b_2={\omega }_{\mathrm{one}}{\omega }_2{x}_{k3}\left({\omega }_{\mathrm{one}}^2-{\omega }_2^2\right)+{\omega }_{\mathrm{one}}{\omega }_3{x}_{k2}\left({\omega }_3^2-{\omega }_{\mathrm{one}}^2\right)+{\omega }_2{\omega }_3{x}_{k\mathrm{one}}\left({\omega }_2^2-{\omega }_5^2\right)$$

;
$$c_2=\left[{\omega }_3^3{x}_{k3}\left({\omega }_2^2-{\omega }_{\mathrm{one}}^2\right)+{\omega }_2^3{x}_{k2}\left({\omega }_{\mathrm{one}}^2-{\omega }_3^2\right)+{\omega }_{\mathrm{one}}^3{x}_{k\mathrm{one}}\left({\omega }_3^2-{\omega }_2^2\right)\right]{\omega }_{\mathrm{one}}{\omega }_2{\omega }_3;$$

$$d_2=\left[{\omega }_3^{}{x}_{k3}\left({\omega }_{\mathrm{one}}^2-{\omega }_2^2\right)+{\omega }_2^{}{x}_{k2}\left({\omega }_3^2-{\omega }_{\mathrm{one}}^2\right)+{\omega }_{\mathrm{one}}^{}{x}_{k\mathrm{one}}\left({\omega }_2^2-{\omega }_3^2\right)\right]{\omega }_{\mathrm{one}}{\omega }_2{\omega }_3,$$

$$x_{0m}=\frac{A{x}_{nm}+B}{C{x}_{nm}+D};$$

$$x_{nm}=\frac{-Y\pm \sqrt{Y^2-\mathrm{four}XZ}}{2X},$$

where A = - (x _22m r _0m + B ₁ ); B = r _nm (A ₁ + r _0m r _22m ) -r _0m -r _11m ; C = r _22m ; D = x _22m r _nm ; X = -r _22m (r _22m r _0m + A ₁ ); Y = r _22m x _11m -B ₁ -x _22m (r _22m r _0m r _0m + A ₁ r _nm ); A ₁ = r _11m r _22m -x _11m x _22m -r _12m r _21m + x _12m x _21m ; B ₁ = x _11m r _22m + r _11m x _22m -x _12m r _21m -r _12m x _21m ;
$$Z=r_{nm}(r_{\mathrm{eleven}m}{r}_{22m}+x_{\mathrm{eleven}m}{x}_{22m})-r_{0m}{r}_{nm}^2(r_{22m}^2+x_{22m}^2)-r_{nm}^2(A_{\mathrm{one}}{r}_{22m}+B_{\mathrm{one}}{x}_{22m})-r_{\mathrm{eleven}m}-r_{0m}+2r_{0m}{r}_{nm}{r}_{22m}+A_{\mathrm{one}}{r}_{nm};$$

x _0m ; x _nm - the optimal values of the imaginary components of the resistances of the source of the input high-frequency signal of the generator and the frequency modulator in the amplification and load conditions for the given four frequencies ω _m = 2πf _m ; m = 1, 2, 3, 4 - frequency number; r _0m - set values of the real component of the resistance of the source of the input high-frequency signal of the generator in the amplification mode at four frequencies; r _nm - set values of the real component of the load resistance at four frequencies; r _11n , x _11m , r _12m , x _12m , r _21m , x _21m , r _22m , x _22m - given values of the total real and imaginary components of the elements of the mixed matrix H of a three-pole nonlinear element and the mixed matrix H of the feedback circuit h _11m = r _11m + jx _11m , h _12m = r _12m + jx _12m , h _21m = r _21m + jx _21m , h _22m = r _22m + jx _22m at given four frequencies and corresponding four values of the amplitude of the low-frequency control signal; k = 0, n is the index characterizing the imaginary components of the load resistance and the signal source in the amplification mode.

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