RU2490774C1 - Power commutation switch - Google Patents

Abstract

FIELD: electricity.

SUBSTANCE: device contains a key (1) with inductor (2) connected in parallel, one output of the inductor forms the first power lead (5) of the commentator switch; at that capacitor (3) in connected in parallel to the switch (1) and an auxiliary inductor (4) is connected in series with its free output forming the second power lead (6) of the commentator switch.

EFFECT: smooth current variation in the commutation circuit and closure of the major converter keys at zero current that makes possible reduction of dynamic losses in power commutator switches of pulse-type regulators, inverters and active front ends.

2 cl, 25 dwg

Description

The invention relates to power electronics, in particular to converters with reduced dynamic losses in power semiconductor switches and can be used in circuits of switching regulators, inverters and active rectifiers.

There is a known converter circuit in which, using elements of a resonant LC circuit, the transistors are gently turned on at zero voltage (see US Patent No. 4,720,668, publ. 01/19/1988).

The disadvantage of this solution is that the pause interval in the circuit is fixed. In this case, the regulation of the output voltage and power in the circuit can only be done by changing the switching frequency.

The closest in technical essence is the solution (see US patent No. 5262930, publ. 16.11.1993), including a power switch with a resonant inductor connected in parallel to it. Connecting a power switch with a parallel resonant inductor in series with the main switch of the converter provides soft switching of the main switch at zero voltage and reduces the energy of dynamic losses in the circuit. Moreover, the circuit uses pulse-width control of the output voltage and power at a constant switching frequency. However, the shutdown process at zero voltage does not allow to effectively reduce the energy of dynamic losses in powerful power switches with a bipolar current transfer mechanism (IGBT, GTO, IGCT). For the practical application of such a solution, a significant slowdown in the rate of change of voltage on the main key is required by connecting a relatively large capacitor to its output circuit of an external capacitor.

The technical result of the device of the present invention is as follows:

1. One auxiliary power switch with a resonant LLC circuit can be used for soft switching of two key elements of the converter at once: the main key and the antiphase one.

2. Connecting an additional capacitor in parallel with the auxiliary power switch allows you to pre-discharge the output capacitance and unlock the main keys of the converter at zero voltage.

3. Connecting an additional inductor in series with the auxiliary power switch allows you to provide a smooth change in current in the switching circuit and lock the main keys of the converter at zero current, which, unlike the closest analogue, eliminates the use of additional capacitors of relatively large capacity, connected in parallel to each of the main keys .

This technical result is achieved due to the fact that in a power switch containing a key with a throttle connected in parallel with it, one of the key leads forms the first power lead of the switch, in accordance with the present invention, a capacitor is connected in parallel with the key, and an additional choke is connected in series, free the output of which forms the second power output of the switch.

In this case, the connection point of the key with the additional inductor can form an additional power output of the switch.

The invention is illustrated by the attached drawings, in which the same elements are denoted by the same reference numerals.

Figure 1 presents the power switch in accordance with the invention.

Figure 2 presents the power switch of figure 1 with an additional power output.

Figure 3 presents a diagram of the closest analogue.

Figure 4 presents the power switch of Figure 1 when it is connected to the base switching circuit in series with the main key.

Figure 5 presents the main oscillograms of the processes of soft switching for the circuit of Figure 4.

Figure 6 presents the power switch of Figure 1 when it is connected to the base switching circuit in series with an antiphase diode.

In Fig.7 presents the main oscillograms of the processes of soft switching for the circuit of Fig.6.

On Fig presents the power switch of figure 2 when it is connected to the basic circuit switching with an additional inductor connected in series with the antiphase diode.

Figure 9 presents the main oscillograms of the processes of soft switching for the circuit of Fig. 8.

Figure 10 presents the power switch of Figure 2 when it is connected to the base switching circuit with an additional inductor, connected in series with the main key.

Figure 11 presents the main waveforms of soft switching processes for the circuit of Figure 10.

Figure 12 presents the power switch of Figure 1, connected in series with the power switch of the DC / DC converter (step-up pulse regulator).

In Fig.13 presents the power switch of Fig.1, connected in series with the antiphase diode of the DC / DC converter (step-up pulse regulator).

On Fig presents the power switch of figure 2, in which the additional inductor is connected in series with the power switch of the DC / DC converter (step-up regulator).

On Fig presents the power switch of figure 2, in which the additional inductor is connected in series with the antiphase diode of the DC / DC converter (boost pulse regulator).

In Fig.16 presents the power switch of Fig.1, connected to a DC circuit of a voltage inverter.

On Fig presents the power switch of figure 1, connected to a DC circuit of an active voltage rectifier.

On Fig presents the power switch of figure 1, connected to the DC circuit of the current inverter in series with unidirectional keys of the key block of the inverter.

In Fig.19 presents the power switch of Fig.1, connected to the DC circuit of the current inverter in series with an additional key.

Figure 20 shows the power switch of Figure 2, connected to the DC circuit of the current inverter (an additional inductor is connected in series with the unidirectional keys of the inverter key block).

On Fig presents the power switch of figure 2, connected to the DC circuit of the current inverter (additional choke is connected in series with an additional key).

On Fig presents three power switch of figure 1, connected to the AC circuit of the voltage inverter in series with the keys of the cathode group of the inverter.

On Fig presents three power switch of figure 1, connected to the AC circuit of the voltage inverter in series with the keys of the anode group of the inverter.

On Fig presents three power switch of Figure 2, connected to the AC circuit of the voltage inverter (additional chokes are connected in series with the keys of the cathode group of the inverter).

On Fig presents three power switch of figure 2, connected to the AC circuit of the voltage inverter (additional chokes are connected in series with the keys of the anode group of the inverter).

The device (FIG. 1) contains: a key 1, a choke 2, a capacitor 3 and an additional choke 4. The drawings also show the first power output 5 and the second power output 6.

The inductor 2 and the capacitor 3 are connected in parallel with the key 1, the additional inductor 4 is connected in series with the key 1, while the positive output of the key 1 forms the first power output 5, and the free output of the additional inductor 4 forms the second power output 6.

As shown in figure 2, the connection point of the key 1 with the additional inductor 4 forms an additional power output 7 of the device.

The proposed device operates as follows.

Consider the work of the power switch when it is connected to the basic switching circuit, to the circuit of which the current switching circuits in voltage regulators, inverters and active rectifiers are reduced (Figure 4). This circuit contains a main switch S with an anti-parallel diode, an antiphase diode D, a current source J and a voltage source E. The power switch with a resonant LLC circuit in accordance with the invention is connected in series to the main key S. Elements of the resonant LLC circuit have the following parameters: inductor 2 — inductance L ₂ ; capacitor 3 - capacity C ₃ ; additional inductor 4 - inductance L ₄ .

At the initial moment of time, the main switch S is turned off, and the power switch 1 is turned on, and through it the initial current of the inductor 2 is closed, which is equal to the value I ₀ . The value of I ₀ will be determined later. According to the state of the keys, the voltage across the capacitor 3 and the current of the additional inductor 4 are equal to zero. The load current J is closed through the antiphase diode D.

Imagine the main intervals of soft switching of the load current from the diode D to the key S and vice versa.

Turning off key 1 at zero voltage and turning on the main key S at zero voltage.

By removing the control signal, turn off the key 1, which due to the parallel connected capacitor 3 turns off at zero voltage. In this case, the current of the inductor 2 begins to charge the capacitor 3:

$$U_{C3}\left(t\right)=I_0{\rho }_{\mathrm{one}}\sin {\omega }_{\mathrm{one}}t\left(\text{one}\right)$$

; $${\omega }_1=1/\sqrt{L_2{C}_3}$$

.Where $${\rho }_{\mathrm{one}}=\sqrt{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">L</figure-callout>}}_2/{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="00000032.png,00000033.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}$$

; $${\omega }_{\mathrm{one}}=\mathrm{one}/\sqrt{L_2{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="00000032.png,00000033.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}$$

.

Then the voltage on the main key S changes in accordance with the formula:

$$U_S\left(t\right)=E-{\mathrm{<figure-callout\; id="0"\; label="I"\; filenames="00000032.png,00000038.png"\; state="\{\{state\}\}">I</figure-callout>}}_0{\rho }_{\mathrm{one}}\sin {\omega }_{\mathrm{one}}t\left(\text{2}\right)$$

If the condition is met:

$$I_0{\rho }_{\mathrm{one}}\ge E\left(\text{3}\right)$$

the main switch S can be turned on at zero voltage due to the voltage drop U _C3 (t) to zero level after a time interval:

$$\Delta t_{\mathrm{one}}=\sqrt{L_2{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="00000032.png,00000033.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}\arcsin E/I_0{\rho }_{\mathrm{one}}\left(\text{four}\right)$$

Turn on key 1 at zero voltage.

After turning on the main key S, an additional inductor 4 enters the operation, while the resonant frequency in the LLC circuit changes, which becomes equal to:

$${\mathrm{<figure-callout\; id="0"\; label="\omega "\; filenames="00000032.png,00000038.png"\; state="\{\{state\}\}">\omega </figure-callout>}}_0=\mathrm{one}/\sqrt{L_0{C}_3}\left(\text{5}\right)$$

.Where $${\mathrm{<figure-callout\; id="0"\; label="L"\; filenames="00000032.png,00000038.png"\; state="\{\{state\}\}">L</figure-callout>}}_0=\frac{L_2{L}_{\mathrm{four}}}{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+L_{\mathrm{four}}}$$

.

The voltage across the capacitor 3 will vary in accordance with the formula:

$$U_{C3}\left(t\right)=E+I_0{\mathrm{<figure-callout\; id="0"\; label="\rho "\; filenames="00000032.png,00000038.png"\; state="\{\{state\}\}">\rho </figure-callout>}}_0\sin {\omega }_{0}t\left(\text{6}\right)$$

.Where $${\mathrm{<figure-callout\; id="0"\; label="\rho "\; filenames="00000032.png,00000038.png"\; state="\{\{state\}\}">\rho </figure-callout>}}_0=\sqrt{{\mathrm{<figure-callout\; id="0"\; label="L"\; filenames="00000032.png,00000038.png"\; state="\{\{state\}\}">L</figure-callout>}}_0/{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="00000032.png,00000033.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}$$

.

Provided:

$$I_0{\mathrm{<figure-callout\; id="0"\; label="\rho "\; filenames="00000032.png,00000038.png"\; state="\{\{state\}\}">\rho </figure-callout>}}_0\ge E\left(\text{7}\right)$$

key 1 can be turned on at zero voltage after a time interval:

$$\mathrm{<figure-callout\; id="2"\; label="\Delta \; t"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">\Delta \; </figure-callout>}{t}_{}{}_2=\sqrt{L_0{C}_3}\left(\pi +\arcsin E/I_0{\rho }_0\right)\left(\text{8}\right)$$

At the end of this interval, the current of the inductor 2 drops to almost zero, and in the main key S, a negative current ΔI ₁ appears, flowing through the counter-parallel diode of the switch S:

$$\Delta I_{\mathrm{one}}=I_0\cos {\omega }_0\Delta t_2\left(\text{9}\right)$$

A linear increase in current in the main key S and turn off the antiphase diode at zero current.

After turning on the key 1, the current of the main key S will change according to a linear law:

$$I_S\left(t\right)=-\Delta I_{\mathrm{one}}+\frac{E}{L_{\mathrm{four}}}t\left(\text{10}\right)$$

After a time interval Δt _{3, the} current of the main switch S reaches the value of the load current, and the antiphase diode D is locked at zero current:

$$\mathrm{<figure-callout\; id="3"\; label="\Delta \; t"\; filenames="00000032.png,00000033.png"\; state="\{\{state\}\}">\Delta \; </figure-callout>}{t}_{}{}_3=\frac{\left(J+\Delta I_{\mathrm{one}}\right)L_{\mathrm{four}}}{E}\left(\text{eleven}\right)$$

Next, the load current J flows through the main switch S, which is in the on state during the conduction interval.

Turning off key 1 at zero voltage and turning on the out-of-phase diode D at zero current.

By removing the control signal, turn off the key 1, which, due to the parallel capacitor 3, turns off at zero voltage. When this voltage on the capacitor 3 changes in accordance with the formula:

$$U_{C3}\left(t\right)=J{\rho }_{\mathrm{one}}\sin {\omega }_{\mathrm{one}}t\left(\text{12}\right)$$

After a time interval Δt _{4, the} voltage U _C3 (t) rises to the voltage E of the source, and the antiphase diode D turns on at zero current, since the load current still flows through the additional inductor 4 and main switch S. The value of Δt ₄ can be determined by the formula:

$$\Delta t_{\mathrm{four}}=\sqrt{L_2{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="00000032.png,00000033.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}\arcsin E/J{\rho }_{\mathrm{one}}\left(\text{13}\right)$$

After a time interval Δt _{4, the} current of the inductor 2 increases to the value:

$$I_{L2}\left(\Delta t_{\mathrm{four}}\right)=J\left(\mathrm{one}-\cos {\omega }_{\mathrm{one}}\Delta t_{\mathrm{four}}\right)=J\left(\mathrm{one}-{\sqrt{\mathrm{one}-\left(E/J{\rho }_{\mathrm{one}}\right)}}^2\right)\left(\text{fourteen}\right)$$

Turn off the main key S at zero current.

After turning on the LLC anti-phase diode, the circuit is connected to the voltage source E.

In this case, the voltage across the capacitor 3 begins to change in accordance with the formula:

$$U_{C3}\left(t\right)=E+J{\rho }_0\sqrt{\mathrm{one}-{\left(E/J{\rho }_{\mathrm{one}}\right)}^2}\sin {\omega }_{0}t\left(\text{fifteen}\right)$$

The current in the inductor 2 varies in accordance with the formula:

$$I_2\left(t\right)=\frac{E}{L_2}t-J\frac{L_{\mathrm{four}}}{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+L_{\mathrm{four}}}\sqrt{\mathrm{one}-{\left(E/J{\rho }_{\mathrm{one}}\right)}^2}\cos {\omega }_{0}t\left(\text{16}\right)$$

The current in the additional inductor 4 and the main key S is changed in accordance with the formula:

$$I_L{}_{\mathrm{four}}\left(t\right)=I_S\left(t\right)=\frac{E}{L_2}t+J\frac{L_2}{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+L_{\mathrm{four}}}\sqrt{\mathrm{one}-{\left(E/J{\rho }_{\mathrm{one}}\right)}^2}\cos {\omega }_{0}t\left(\text{17}\right)$$

If the condition is met:

$$J\frac{L_2}{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+L_{\mathrm{four}}}\sqrt{\mathrm{one}-{\left(E/J{\rho }_{\mathrm{one}}\right)}^2}\ge \frac{\mathrm{<figure-callout\; id="2"\; label="E\; L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">E\; </figure-callout>}}{L_{}}\pi \sqrt{L_0{C}_3}\left(\text{eighteen}\right)$$

the current of the additional choke 4 reaches zero, and the main switch S can be turned off at zero current.

In this interval, a negative current appears in the main key S, flowing through its counter-parallel diode. The amplitude of the negative current is determined by the expression:

$$\Delta I_2=\frac{\mathrm{<figure-callout\; id="2"\; label="E\; L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">E\; </figure-callout>}}{L_{}}\pi \sqrt{L_0{C}_3}-J\frac{L_2}{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+L_{\mathrm{four}}}\sqrt{\mathrm{one}-{\left(E/J{\rho }_{\mathrm{one}}\right)}^2}\left(\text{19}\right)$$

The duration of the shutdown interval of the main key S at zero current is determined by the formula:

$$\mathrm{<figure-callout\; id="5"\; label="\Delta \; t"\; filenames="00000029.png,00000031.png"\; state="\{\{state\}\}">\Delta \; </figure-callout>}{t}_{}{}_5=\sqrt{L_0{C}_3}\left(\pi +\arcsin E/J{\rho }_0\right)\left(\text{twenty}\right)$$

After turning off the main key S, the current of the inductor 2 increases to the value:

$$I_{L2}\left(\Delta t_5\right)=J\left(\mathrm{one}-\sqrt{\mathrm{one}-{\left(E/J{\rho }_{\mathrm{one}}\right)}^2}\right)+J\frac{L_{\mathrm{four}}}{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="00000033.png,00000034.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+L_{\mathrm{four}}}\sqrt{\mathrm{one}-{\left(E/J{\rho }_{\mathrm{one}}\right)}^2}\sqrt{\mathrm{one}-{\left(E/J{\rho }_0\right)}^2}+\frac{E}{{\omega }_0{L}_2}\left(\pi +\arcsin \frac{E}{J{\rho }_0}\right)\left(21\right)$$

Note that the voltage across the capacitor 3 at the end of the interval Δt ₅ drops to almost zero.

Recovery of the initial energy in the LLC circuit and the inclusion of key 1 at zero voltage.

When the main key S and key 1 are off in a parallel LC circuit formed by the inductor 2 and the capacitor 3, an oscillatory process begins with a frequency of ω ₁ :

$$\{\begin{array}{c}{I}_{L2}\left(t\right)=I_{L2}\left(\Delta t_5\right)\cos {\omega }_{\mathrm{one}}t\\ U_{C3}\left(t\right)=I_{L2}\left(\Delta t_5\right){\rho }_{\mathrm{one}}\sin {\omega }_{\mathrm{one}}t\end{array}\left(\text{22}\right)$$

Thus on the capacitor 3 appears negative with respect to the key 1 voltage. After half the period of the resonant frequency ω _{1, the} voltage across the capacitor 3 drops to zero, and the current of the inductor 2 reaches the initial value I _L2 (Δt ₅ ), but with the opposite sign. Thus, in the inductor 2, the initial current value I _{0 is} restored, from which the switching cycle began:

$$I_0=-I_{L2}\left(\Delta t_5\right)\left(\text{23}\right)$$

Obviously, the control pulse for key 1 must be supplied during the half-cycle under consideration, then at the end of it the key 1 will automatically turn on at zero voltage.

After restoring the initial energy in the LLC circuit, you can start a new switching cycle, etc.

The main oscillograms of soft switching processes for the considered option are presented in Fig. 5, which were obtained using the circuit simulation program PSpice with the following circuit parameters:

Supply voltage E = 80 V.

Load current J = 40 A.

Choke 2 - inductance 6.5 μH.

Choke 4 - inductance 1.0 μH.

Capacitor 5 - 0.1 μF capacitance.

Vertical Scale:

Channel 1: voltage on key S; 200 B / div

Channel 2: key current S; 100 A / div

Channel 3: voltage on key 1 and capacitor 3; 200 B / div

Channel 4: current of key 1; 100 A / div

Channel 5: inductor current 2; 100 A / div

Horizontal Scale:

Time - 4 μs / div.

The conditions of soft switching in the circuit do not change if the power switch with a resonant LLC circuit is removed from the serial connection circuit with the key S and connected in series to the antiphase diode circuit D (Figure 6). This statement follows from the fact that the system of equations describing the electrical processes in the circuit remains unchanged, and the current and voltage of the switch S when moving the power switch with a resonant LLC circuit into the circuit of the diode D are still independent variables. The main oscillograms of soft switching processes for this option are shown in Fig. 7, which were obtained using the circuit simulation program PSpice with the following circuit parameters:

Supply voltage E = 500 V.

Load current J = 40 A.

Choke 2 - inductance 6.5 μH.

Choke 4 - inductance 1.0 μH.

Capacitor 5 - 0.1 μF capacitance.

Vertical Scale:

Channel 1: voltage on key S; 200 B / div

Channel 2: key current S; 100 A / div

Channel 3: voltage on key 1 and capacitor 3; 200 B / div

Channel 4: current of key 1; 100 A / div

Channel 5: inductor current 2; 100 A / div

Horizontal Scale:

Time - 4 μs / div.

The soft switching conditions in the circuit do not change if the additional inductor 4 is removed from the serial connection circuit with the key S and, using the additional power output 7, is connected in series to the antiphase diode D circuit (Fig. 8). This statement follows from the fact that the system of equations describing the electrical processes in the circuit remains unchanged, and the current and voltage of the switch S when moving the additional inductor 4 into the circuit of the diode D are still independent variables. The main oscillograms of soft switching processes for this option are presented in Fig. 9, which were obtained using the PSpice circuit simulation program with the following circuit parameters:

Supply voltage E = 500 V.

Load current J = 40 A.

Choke 2 - inductance 6.5 μH.

Choke 4 - inductance 1.0 μH.

Capacitor 5 - 0.1 μF capacitance.

Vertical Scale:

Channel 1: voltage on key S; 200 B / div

Channel 2: key current S; 100 A / div

Channel 3: voltage on key 1 and capacitor 3; 200 B / div

Channel 4: current of key 1; 100 A / div

Channel 5: inductor current 2; 100 A / div

Horizontal Scale:

Time - 4 μs / div.

Soft switching conditions in the circuit do not change if the key 1 with the inductor 2 and the capacitor 3 connected in parallel to it is removed from the serial connection circuit with the key S and, using the additional power output 7, is connected in series to the antiphase diode D circuit (Figure 10). This statement follows from the fact that the system of equations describing the electrical processes in the circuit remains unchanged, and the current and voltage of the switch S when moving the switch 1 with the inductor 2 and the capacitor 3 connected in parallel to it in the circuit of the diode D are still independent variables . The main oscillograms of soft switching processes for this option are presented in Fig. 11, which were obtained using the PSpice circuit simulation program with the following circuit parameters:

Supply voltage E = 500 V.

Load current J = 40 A.

Choke 2 - inductance 6.5 μH.

Choke 4 - inductance 1.0 μH.

Capacitor 5 - 0.1 μF capacitance.

Vertical Scale:

Channel 1: voltage on key S; 200 B / div

Channel 2: key current S; 100 A / div

Channel 3: voltage on key 1 and capacitor 3; 200 B / div

Channel 4: current of key 1; 100 A / div

Channel 5: inductor current 2; 100 A / div

Horizontal Scale:

Time - 4 μs / div.

The principle of operation of a power switch with a resonant LLC circuit does not change when using different types of keys: bipolar and field-effect transistors, thyristors, bipolar transistors with an insulated gate - IGBT, etc.

Next, we consider options for specific applications of the proposed device.

In step-up DC-DC converters, the switching circuit consists of a main transistor T, an antiphase diode D, a voltage source at the output filter capacitor Cf, and a current source in the input choke Lf. Connecting a power switch with a resonant LLC circuit in accordance with the present invention (Figs. 12, 13, 14, 15) allows for soft switching of the key elements of the converter.

On Fig presents a power switch with a resonant LLC circuit of figure 1, connected in series with the power switch of the DC / DC converter (step-up regulator).

On Fig presents a power switch with a resonant LLC circuit of Fig.1, connected in series with the antiphase diode of the DC / DC converter (step-up regulator).

On Fig presents a power switch with a resonant LLC circuit of Figure 2, an additional inductor is connected in series with the power switch of the DC / DC converter (step-up regulator).

On Fig presents a power switch with a resonant LLC circuit of Figure 2, an additional inductor is connected in series with the antiphase diode of the DC / DC converter (step-up regulator).

In three-phase voltage inverters, an additional switch Ta in the DC circuit of the inverter, counter-parallel diodes of the inverter key unit, input voltage source E and inverter input current form a switching circuit to which, in accordance with the present invention, a power switch with a resonant LLC circuit can be connected. On Fig presents a power switch with a resonant LLC circuit of figure 1, connected to the DC circuit of the voltage inverter in series with an additional switch Ta.

In three-phase active voltage rectifiers, an additional diode Da in the inverter DC circuit, the main keys of the key block of the active rectifier, the output voltage source on the filter capacitor Cf and the output current of the active rectifier form a switching circuit to which a power switch can be connected with in accordance with the present invention resonant LLC circuit. On Fig presents a power switch with a resonant LLC circuit of figure 1, connected to a DC circuit of an active voltage rectifier in series with an additional diode Da.

In three-phase current inverters, an additional switch Ta in the DC circuit of the inverter, unidirectional keys of the inverter key block, the input current source on the filter choke Lf and the voltage at the inverter input form a switching circuit to which in accordance with the present invention (Figs. 18, 19, 20 , 21) a power switch with a resonant LLC circuit can be connected.

On Fig presents a power switch with a resonant LLC circuit of figure 1, connected to the DC circuit of the current inverter in series with unidirectional keys of the key block of the inverter.

On Fig presents a power switch with a resonant LLC circuit of figure 1, connected to the DC circuit of the current inverter in series with an additional key.

On Fig presents a power switch with a resonant LLC circuit of figure 2, connected to the DC circuit of the current inverter (additional choke is connected in series with the unidirectional keys of the key block of the inverter).

On Fig presents a power switch with a resonant LLC circuit of Fig.2, connected to the DC circuit of the current inverter (an additional inductor is connected in series with an additional key).

On the AC side of three-phase voltage inverters, the upper and lower key in the key rack of each of the inverter phases, the constant voltage source E and the inverter phase current form a switching circuit to which, in accordance with the present invention (Figs. 22, 23, 24, 25), be connected power switch with a resonant LLC circuit.

On Fig presents three power switch with a resonant LLC circuit of figure 1, connected to the AC circuit of the voltage inverter in series with the main keys of the cathode group of the inverter. In this case, the switching of the main keys of the anode group is carried out using the same power switches with a resonant LLC circuit, which for the keys of the anode group can be considered as connected in series with their antiphase diodes, which are counter-parallel diodes of the main keys of the cathode group.

On Fig presents three power switch with a resonant LLC circuit of figure 1, connected to the AC circuit of the voltage inverter in series with the main keys of the anode group of the inverter. In this case, the switching of the main keys of the cathode group is carried out using the same power switches with a resonant LLC circuit, which for the keys of the cathode group can be considered as connected in series with their antiphase diodes, which are counter-parallel diodes of the main keys of the anode group.

On Fig presents three power switch with a resonant LLC circuit of figure 2, connected to the AC circuit of the voltage inverter (additional chokes are connected in series with the keys of the cathode group of the inverter). In this case, the switching of the main keys of the anode group is carried out using the same power switches with a resonant LLC circuit, which for the keys of the anode group can be considered as a solution according to Figure 2 with additional chokes connected in series with their antiphase diodes, which are counter-parallel diodes of the main keys of the cathode group.

On Fig presents three power switch with a resonant LLC circuit of figure 2, connected to the AC circuit of the voltage inverter (chokes are connected in series with the keys of the anode group of the inverter). In this case, the switching of the main keys of the cathode group is carried out using the same power switches with a resonant LLC circuit, which for the keys of the cathode group can be considered as a solution according to Figure 2 with additional chokes connected in series with their antiphase diodes, which are counter-parallel diodes of the main keys of the anode group.

Claims (2)

1. A power switch containing a key with a throttle connected in parallel with it, one of the key leads forms the first power lead of the switch, characterized in that a capacitor is connected in parallel with the key and an additional choke is connected in series, the free lead of which forms the second power lead of the switch. 2. The power switch according to claim 1, characterized in that the connection point of the key with the additional inductor forms an additional power output of the switch.

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