RU2450422C1 - Multichannel adaptive radio-receiving device - Google Patents

Abstract

FIELD: radio engineering.

SUBSTANCE: device comprises a unit of weighted addition, an antenna array, a unit to generate weight coefficients, a unit to fix weight coefficients, a unit to estimate spatial parameters with the first and second input mount buses, and a unit of time-frequency processing.

EFFECT: invention provides for simultaneous reception of signals of all specified sources of radio emissions with pseudorandom tuning of working frequency with simultaneous increase of quality of their reception due to higher probability of right selection of an input flow of signals by means of accounting of their spatial parameters.

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Description

The invention relates to the field of radio engineering, in particular to multi-channel adaptive radio receivers, and can be used in radio communication systems, radars, operating in a complex signal-jamming environment.

Various types of multichannel adaptive radio receivers based on adaptive antenna systems (AAS) are known: with forward control, using correlation feedbacks, modulation type, etc. Adaptive antenna systems of modulation type, which have a number of advantages, contain an antenna array, a weighted addition unit ), a block for the formation of weighting coefficients (BFVK) and a block for frequency-time processing (BSWO) (see Monzingo, R.A., Miller, T.U., Adaptive Antenna Arrays: Introduction to Theory. - M.: Radio and Communication, 1986,p.448). These systems provide the formation of two voltages proportional to signal and interference levels.

The disadvantage of these devices is their relatively low speed when using signals with pseudo-random tuning of the operating frequency (frequency hopping).

A multi-channel adaptive radio receiver is known (see Pat. RF No. 2066925, IPC Н04В 1/06, publ. September 20, 1996). It contains a series-connected weighted addition unit and a time-frequency processing unit, the first and second outputs of which are connected respectively to the inputs of the estimation of the useful and interference components of the input signals of the weighting unit, each of the N outputs of which is connected to the corresponding input of the weighted addition, to the other The N inputs of which the outputs of the N antenna elements are connected, while the outputs of the time-frequency processing unit are the output of the device.

An analog device provides the reception of signals from all frequency hopping radios using common frequencies. For signal selection of various sources of radio emissions (IRI), it uses information about the phase of the cyclic synchronization of various radio equipment (see Nikitchenko V.V., Smirnov P.L. Combined methods of noise protection (using adaptive antenna systems and signals with pseudo-random frequency tuning). Foreign Radio Electronics, 1988, No. 5, pp. 24-31).

The disadvantage of the analogue is its long-term entry into communication due to the fact that the AAS radiation pattern is frequency-dependent. The high rate of change of frequencies at which information is transmitted involves the use of a high-speed adaptation algorithm. Otherwise, the AAS will constantly be in transition mode.

The closest in technical essence to the claimed device is a multi-channel adaptive radio receiver (see Pat. RF №2107394, IPC Н04В 7/02, H01Q 21/00, publ. 20.03.1998). It contains a weighted addition unit and a time-frequency processing unit, the information input of which is connected to the information output of the weighted addition unit, and the group of information outputs is the device output bus, an antenna array made of N> 2 identical non-directional antenna elements, the outputs of which are connected to the first a group of information inputs of a weighted addition unit, a unit for generating weight coefficients, the first group of information outputs of which are connected to a second group of information the inputs of the weighted addition block, and the inputs of the estimation of the useful and noise components of the signal are connected to the corresponding outputs of the useful and noise components of the signal of the time-frequency processing unit, a weight fixing block, the first group of information inputs of which is connected to the second group of information outputs of the weight coefficients, a group of information inputs of which is connected to a group of information outputs of a block for fixing weight coefficients, and the first and second control All inputs are connected respectively to the first and second control outputs of the unit, fixing weighting factors.

The prototype device provides a higher speed adaptation algorithm, which ultimately allows the reception of IRI signals with frequency hopping. The latter was made possible by taking into account a priori information about the signal-noise situation at the frequencies used in the preceding instants of time. Moreover, it is an AAS that implements a minimax spatial signal processing algorithm. The device provides the formation of a radiation pattern, the maximum of which tracks the direction to the correspondent, and the minima are oriented in the direction of the interference sources. The use of data on the signal-noise situation allowed in the prototype device to increase the ratio η signal / (interference + noise) at its output.

However, the prototype device also has disadvantages. In the presence of K reception channels (the number of used frequencies of IRI with frequency hopping), the prototype provides the reception of signals of only one IRI. In addition, the prototype has a disadvantage associated with the relatively low quality of reception of IRI signals. Here, the reception quality is characterized by the probability of error-free selection (collection) of IRI signals with frequency hopping transmitted at different frequencies, from their combination. It should be noted that the quality of reception of IRI signals with frequency hopping in the prototype device depends on:

loading a common band of operating frequencies (the number of IRI with frequency hopping operating at common frequencies);

features of the propagation of radio waves in the deployment area (the presence of a rugged or mountainous terrain, urban development, etc., leading to multipath propagation of radio waves).

The aforementioned causes lead to errors in the selection of signals given by the IRI with frequency hopping, and, consequently, to a decrease in the quality of signal reception η. In some cases, to reduce intra-system interference, orthogonal communication systems with frequency hopping are used, in which the general synchronization of radio networks operating at common frequencies is provided (see Klimenko N.N. VHF radio stations: status, development prospects, features of applying the frequency hopping mode .-- Foreign Electronics, No. 8, 1990, p.20-32). Under these conditions, the prototype loses its performance.

The aim of the proposed technical solution is to develop a device that provides the simultaneous reception of signals of all given IRI with frequency hopping, operating at common frequencies, while improving the quality of their reception by increasing the probability of correct selection of the input stream by taking into account the spatial parameters of the received radiation.

This goal is achieved by the fact that in a multi-channel adaptive radio receiving device containing a weighted addition unit, a time-frequency processing unit, the information input of which is connected to the information output of the weighted addition unit, and the group of information outputs is the device output bus, an antenna array made of N> 2 identical omnidirectional antenna elements, the outputs of which are connected to the first group of information inputs of the weighted addition unit, a weighting coefficient generating unit Comrade, the first group of information outputs of which is connected to the second group of information inputs of the weighted addition block, and the inputs for evaluating the useful and noise components of the signal are connected to the corresponding outputs of the useful and noise components of the signal of the time-frequency processing unit, the block for fixing weight coefficients, the group of information inputs of which are connected with the second group of information outputs of the weighting coefficient forming unit, the group of information inputs of which is connected to the group of info mation outputs of the unit for fixing the weighting coefficients, and the first and second control inputs are connected respectively to the first and second control outputs of the unit for fixing the weighting factors, an additional unit for estimating spatial parameters is introduced, the first group of information inputs of which is combined with the first group of information inputs of the unit of weighted addition outputs connected to the group of address inputs of the time-frequency processing unit and the group of address inputs of the block fixing the weight coefficient NTV, the first and second K-channel groups of control outputs of which are connected respectively with the first and second K-channel groups of control inputs of the weighting unit, where K is the number of receiving channels of the time-frequency processing block, K >> 1, and the second and third groups of information inputs of the spatial parameter estimation unit are the first and second input installation buses of the device, respectively, and the time-frequency processing unit is made up of M signal adders, M> 1, the outputs of which are the group of information outputs of the block, the first code converter, the group of information inputs of which is the group of address inputs of the block, and K receiving channels, K> M, the information inputs of which are combined and are the information input of the time-frequency processing block, M signal outputs of each of the receiving channels connected to the corresponding inputs of the M signal adders, the outputs of the useful component of the signal K of the receiving channels are a group of outputs of the useful component of the signal of the block, the outputs of the interference The receiving K receiving channels are the group of outputs of the interfering component of the signal of the block, the groups of address inputs of K receiving channels are bitwise combined and connected to the group of outputs of the first code converter, with each receiving channel containing a series-connected bandpass filter, a delay element, a key, and a first switch, M outputs which are the information outputs of the receiving channel, and the input of the band-pass filter is the information input of the receiving channel, the second switch, amplitude detector and RS-trigger, the path of which is connected to the control inputs of the key and the second switch, the first output of which is the output of the useful component of the channel signal, the second output is the noise component of the channel signal, and the information input of the second switch is connected to the output of the amplitude detector, the input of which is connected to the output of the bandpass filter, connected in series a pulse shaper, a waiting multivibrator, a second code converter, the address input troupe of which is combined with the address input group of the first switch a group address of the reception channel inputs, and the pulse shaper output is connected to the second input of the RS-flip-flop, a first input coupled to an output of the second code converter.

The block for fixing the weight coefficients is made up of a decoder, J fixation channels, J> K, K first adders, K second adders and K third adders, the group of information inputs of the decoder being a group of address inputs of the block, and KJ groups of outputs with sets of K groups connected to the corresponding K groups of address inputs J channels of fixation, K groups of information outputs of each of which are connected to the corresponding groups of information inputs K of the first adders, groups of information outputs of which are g Uppa information outputs of the block, and KJ groups of information inputs of all J channels of fixation are a group of information inputs of the block, K outputs of the first control signal of each channel of fixation are connected to the corresponding inputs of K second adders, the outputs of which are the first group of control signals, block, K outputs of the second control the signals of each latch channel are connected, with the corresponding inputs K of the third adders, the outputs of which are the second group of control signals of the block, and each latch channel contains a memory block and K processing paths, and K groups of address inputs of the memory block are combined with groups of address inputs of the corresponding processing paths and at the same time are K groups of address inputs of the channel, K groups of information outputs of the memory block are connected to groups of information inputs of the corresponding processing paths, the first control outputs which are connected to the corresponding first control inputs of the memory unit, the second control inputs of which are connected to the second control outputs of the corresponding processing channels, the group of information outputs of the processing paths are the group of information outputs of the channel, the third control outputs of the processing paths are the group of outputs of the first channel control signal, and the fourth outputs of the control of processing paths are the group of outputs of the second channel control signal, K-1 of the blocking channel inputs are connected to the outputs blocking the corresponding paths of K-1 channels, and the blocking output is connected to the blocking inputs of the corresponding paths of K-1 channels, with each path the bobbin contains a series-connected code converter, a pulse selector and a block of AND elements, the group of inputs of which is a group of information inputs of the path, and the group of information outputs is a group of information outputs of the path, the group of inputs of the code converter is the address group of the path, and the output is the first output of the path control, a pulse shaper, the first and second delay elements, the output of which is the second control output of the path, and the input is connected to the output of the pulse shaper and is I have the fourth output of the path control, the input of the first delay element is connected to the output of the code converter, and the output of the first delay element is the third output of the path control, K-1 of the control inputs of the pulse selector are K-1 blocking inputs of the path, the second output of the pulse selector is the blocking output of the path and the first output of the pulse selector is connected to the input of the pulse shaper.

The listed new set of essential features due to the fact that new blocks and communications are being introduced allows achieving the purpose of the invention: to provide simultaneous reception of signals of all given IRI with frequency hopping operating at common frequencies, while improving the quality of their signal reception.

The inventive device is illustrated by drawings, which show:

figure 1 is a structural diagram of a multi-channel adaptive radio receiver and frequency-time processing unit;

figure 2 is a structural diagram of a unit for assessing spatial parameters;

figure 3 - frequency bearing panorama;

figure 4 is a structural diagram of a block fixing weighting factors;

figure 6 is a structural diagram of the path of formation of weighting factors;

7 is an embodiment of a pulse selector;

7 is an embodiment of a comparison unit.

The inventive device (see Fig. 1) contains a weighted addition unit 1, a time-frequency processing unit 6, the information input of which is connected to the information output of the weighted addition unit 1, and the group of information outputs is an output bus of a multi-channel adaptive radio receiving device, antenna array 2, made of N> 2 identical non-directional antenna elements, the outputs of which are connected to the first group of information inputs of the weighted addition unit 1, the unit for generating weighting factors 3, the first load PP information outputs of which are connected to the second group, information inputs of the weighted addition unit 1, and inputs for evaluating the useful and interference components of the signal are connected to the corresponding outputs of the useful and interference components of the signal of the time-frequency processing unit 6, a block for fixing weighting factors 4, the group of information inputs of which connected to the second group of information outputs of the weighting unit 3, the group of information inputs of which is connected to the group of information the outputs of the unit for fixing the weighting factors 4, and the first and second control inputs are connected respectively to the first and second control outputs of the unit for fixing the weighting factors 4.

To ensure the simultaneous reception of signals of all IRI with frequency hopping, operating at common frequencies, while reducing the time of entering into communication by taking into account the spatial parameters of the received signals, an additional block for estimating spatial parameters 5 is introduced, the first group of information inputs of which are combined with the first group of information inputs of the block weighted addition 1. The group of address outputs of block 5 is connected to the group of address inputs of block of time-frequency processing 6 and the group of address inputs of block f 4 x weighting factors, the first and second K-channel groups of control outputs of which are connected respectively to the first and second. K-channel groups of control inputs of the unit for generating weight coefficients 3. The value of K is determined by the number of receiving channels 12 of the time-frequency processing unit 6, K >> 1. The second 7 and third 9 groups of information inputs of block 5 are the first and second input installation buses of a multi-channel adaptive radio receiving device, respectively.

The time-frequency processing unit 6 contains M signal adders 10.1-10.M, M> 1, the outputs of which 8.1-8.M are the outputs of the time-frequency processing unit 6. The first code converter 11, the group of information inputs of which is a group of address inputs of the block 6. In addition, block 6 has K receiving channels 12.1-12.K, K> M, K >> 1 whose information inputs are combined and are information input 6, and M signal outputs of each of the receiving channels 12.1-12.K are connected to the corresponding inputs M of the signal adders 10.1-10.M The outputs of the useful component of the signal K of the receiving channels 12.1-12.K are the group of outputs of the useful component of the signal of the block 6. The outputs of the interfering component of the signal K of the receiving channels 12.1-12.K are the group of outputs of the interference component of the signal of the block 6. Groups of address inputs K of the receiving channels 12.1-12. K is bitwise combined and connected to the group of outputs of the first code converter 11. Moreover, each receiving channel 12.1-12.K contains a series-pass bandpass filter 13, a delay element 14, a key 15, and a first switch 16, the M outputs of which are information the outputs of each receive channel 12.1-12K, and the input of the band-pass filter 13 is the information input of each receive channel 12.1-12K. The second switch 19, the amplitude detector 18, RS-trigger 17, the output of which is connected to the control inputs of the key 15 and the second switch 19. The first output of the block 19 is the output of the useful component of the signal of the receiving channel 12.1-12.K, and the second output is the interference component of the signal receiving channel 12.1-12.K. The information input of block 19 is connected to the output of the amplitude detector 18, the input of which is connected to the output of the bandpass filter 13. In addition, block 6 includes serially connected pulse shaper 20, waiting for the multivibrator 21, the second code converter 22, the group of address inputs of which is combined with the group address inputs of the first switch 16 and is an address group of inputs of the receiving channel 12.1-12.K. The output of block 20 is connected to the second input of the RS flip-flop 17, the first input of which is connected to the output of the second code converter 22.

The weight fixing block 4 (see Fig. 4) is made comprising a decoder 38, J of fixing channels 39.1-39.J, J> K, K of the first adders 42.1-42.K, K of the second adders 43.1-43.K and K of the third adders 44.1-44.K. Moreover, the group of information inputs of the decoder 38 is a group of address inputs of block 4, and KJ groups of outputs by sets of K groups are connected to the corresponding K groups of address inputs J channels of fixation 39.1-39K, K groups of information outputs of each of which are connected to the corresponding groups of information inputs K of the first adders 42.1-42.K. The information output groups of the first adders 42.1-42.K are the information output group of block 4, and the KJ information input groups of all J latch channels are the information input group of block 4, K outputs of the first control signal of each latch channel 39 are connected to the corresponding inputs K of the second adders 43.1 -43.K. The outputs of blocks 43.1-43.K are the first group of control signals of block 4, K of the outputs of the second control signal of each latch channel 39.1-39.J are connected to the corresponding inputs K of the third adders 44.1-44.K, the outputs of which are the second group of control signals of block 4 .

Each latch channel 39 contains a memory block 40 and K of the processing paths 41.1-41.K, and K groups of address inputs of the memory block 40 are combined with groups of address inputs of the corresponding processing paths 41 and at the same time are K groups of address inputs of the channel 39. K groups of information outputs of the block memory 40 are connected to groups of information inputs of corresponding processing paths 41, the first control outputs of which are connected to the corresponding first control inputs of memory unit 40. The second control inputs of memory block 40 are connected to the control outputs of the respective processing paths 41. The information outputs of the processing paths 41 are the group of information outputs of the channel 39. The third control outputs of the processing paths 41 are the group of outputs of the first channel control signal 39, and the fourth control outputs of the processing paths 41 are the group of outputs of the second channel control signal 39. K-1 blocking inputs of the processing path 41 are connected to the blocking outputs of the corresponding processing paths 41 of the other K-1 channels 39, and the blocking output is connected nen block with inputs corresponding processing paths 41 K-1 other channels 39.

Each processing path 41 contains a series-connected code converter 45, a pulse selector 46 and a block of elements AND 50, the group of information inputs of which is a group of information inputs of the path 41, and the group of information outputs is a group of information outputs of the path 41. The group of inputs of the code converter 45 is an address group tract 41, and the output is the first control output of the path 41. Pulse generator 47, the first and second delay elements 49 and 48, respectively. The output of block 48 is the second control output of the path 41, and the input is connected to the output of the pulse shaper 47 and is the fourth control output of the path 41. The input of the first delay element 49 is connected to the output of the code converter 45, and its output is the third control output of the path 41. K- 1, the control inputs of the pulse selector 46 are K-1 blocking inputs of the path 41, the second output of the pulse selector 46 is the blocking output of the path 41, and the first output of the pulse selector is connected to the input of the pulse shaper 47.

The spatial parameter estimation unit 5 contains (see FIG. 2) an antenna switch 26, N inputs of which are connected to the corresponding N outputs of the antenna array 2, and the signal and reference outputs of the antenna switch 26 are connected respectively to the signal and reference inputs of the radio receiving device 27, made by circuit with common local oscillators. The block of analog-to-digital conversion 28 is made two-channel, respectively, with signal and reference channels, and the signal and reference outputs of the intermediate frequency of the radio receiving device 27 are connected respectively to the signal and reference inputs of the block of analog-to-digital conversion 28. The Fourier transform unit 29 is made of two-channel, respectively, with signal and reference channels. In addition, block 5 contains first 25 and second 31 storage devices, a subtracting unit 32, a unit for generating phase differences 24, a unit for calculating phase differences 30, the first information input of which is connected to the signal output of the Fourier transform unit 29, and the second input to the reference the output of the Fourier transform unit 29. The group of information outputs of the phase difference calculation unit 30 is connected to the group of information inputs of the second storage device 31, the group of information outputs of which is connected to the group of inputs of the subtraction unit 32. The group of inputs of the reduced unit of subtraction 32 is connected to the information outputs of the first storage device 25, the information inputs of which are connected to the information outputs of the unit for generating the phase differences 24. The group of information inputs of the block 24 is the first input installation bus 7 of the device. Serially connected multiplier 33, adder 34, third storage device 35, azimuth determination unit 36 and comparison unit 37, the second group of information inputs of which is the second input installation bus 9 of the device, the third group of information inputs of block 37 is connected to the group of address outputs of the radio receiver 27, and the group of information outputs is a group of address outputs of block 6. The first and second groups of information inputs of the multiplier 33 are combined and connected to the group of information outputs of the block subtraction 32. The output of the clock generator 23 is connected to the control input of the antenna switch 26, the synchronization inputs of the analog-to-digital conversion unit 28, the Fourier transform unit 29, the first, second and third storage devices 25, 31 and 35, respectively, the subtraction unit 32, the multiplier 33 , adder 34. azimuth determination unit 36, a unit for generating phase differences 24 and a unit for calculating phase differences 30.

The comparison unit 37 (see Fig. 8) contains the first memory block 66, M of the comparison paths 67.1-67.M and the first adder 68. The first group of information inputs of the first memory block 66 is the second group of information inputs of the block 37. M groups of information outputs of the block 66 are connected to the corresponding first groups of information inputs of the comparison paths 67. The second groups of information inputs of the comparison paths 67 are bitwise combined and are the first information group of inputs of the block 37. The third groups of information inputs of the comparison paths 67 are are combined and are the third group of information inputs of block 37. The first groups of information outputs of comparison paths 67 are connected to the corresponding second groups of information inputs of the first memory block 66. The second groups of information outputs of comparison paths 67 are connected to the corresponding groups of inputs of the first adder 68, the group of information outputs of which is a group of information outputs of block 37. In this case, the M control inputs of the first memory block 66 are connected to the control outputs respectively compare paths 67.

Each comparison path 67 (see Fig. 8) contains a second memory block 74, a second adder 69 and a divider 72 in series, the group of information outputs of which is the first group of information outputs of the comparison path 67, and the group of information inputs of the second memory block 74 is the second group information inputs of the comparison path 67. The comparison element 70 and the third adder 71, the first groups of information inputs of which are combined and are the first group of information inputs of the comparison path 67. The second group of information one of the inputs of the comparison element 70 is combined with the group of information inputs of the second adder 69, and the output is connected with the counting input of the pulse counter 73, the control input of the second memory unit 74 and the control input of the third adder 71. The second group of information inputs of the third adder 71 is the third group of information inputs of the path 67, and the group of information outputs - the second group of information outputs of the comparison path 67. The group of information outputs of the pulse counter 73 is connected to the second group of inform tional input divider 72, and the pulse generator output 75 is a control path 67 output comparison.

и помехового

показателей качества.The weight generation unit 3 (see FIG. 5) contains K identical channels for generating the weight coefficients 51.1-51.K. Each channel 51 contains N groups of information inputs, which are part of the group NK information inputs of block 3, TV groups of information outputs, which are part of the NK second group of information outputs of block 3. N outputs of the weight coefficients of block 51 are part of NK first information outputs of the block 3. In addition, each channel for generating weighting coefficients 51 contains inputs of the first and second control signals corresponding to this channel for generating weighting coefficients 51.i, as well as inputs of corresponding Besides the signaling channel 51.i

and interfering

quality indicators.

Each channel for the formation of weighting coefficients 51 (see Fig. 5) contains N adaptation paths 52.1-52.N the first adder 53. The first and second inputs of the first adder 53 are the signal inputs U _C and interference U _P quality indicators of block 51. The output of the first adder 53 is connected to the evaluation inputs of all adaptation paths 52.1-52.N of the channel for generating weight coefficients 51. The first inputs of the adaptation paths are combined and are the input of the first control signal of block 51. The second control inputs of the adaptation paths 52.1-52.N are combined and are the input to orogo control unit 51. The group of information inputs of each path to adapt the signal 52 is one of N groups of information inputs a channel 51 forming weight coefficients.

The first group of information outputs of each adaptation path 52 is one of the N groups of information outputs of block 51. The second information output of each adaptation path 52 is one of N outputs of the weight coefficients of block 51.

Each adaptation path 52 (see Fig. 6) contains a series-connected multiplier 61, an integrator 59, a second switch 58 and an analog-to-digital converter 57, the group of information outputs of which is a group of information outputs of the adaptation path 52, and the input of the multiplier 61 is an input of the path estimation adaptation 52. Serially connected digital-to-analog Converter 54, the first key 55 and the second adder 56, the output of which is the second information output of the adaptation path 52. The second input of the second adder 56 is combined with the second input multiplier 61 and the output of the perturbation generator 60 sequence, and a third input connected to the output of the integrator 59. The input of the first control key 55 is an input first control signal adaptation path 52 and the second control input key 58 - the control input of the second adaptation signal path 52.

The implementation of blocks 1 and 2 is known and widely covered in the literature. They can be implemented similarly to the corresponding blocks of the prototype device.

The complexity of the signal-noise environment (SPO) and its high dynamism, characteristic of the simultaneous reception of signals from several IRI with frequency hopping, determine the appropriateness of the "assessment-adaptation" approach (see Nikitchenko V.V., Smirnov P.L. Estimation of spatial polarization parameters of signals and interference when receiving radiation with a pseudo-random tuning of the operating frequency. -Radiotekhnika i Elektronika, 1990, vol. 35, No. 4, p. 767-774.). It consists in assessing the spatial parameters of radio signals, making decisions about whether each IRI belongs to useful or interfering, and calculating optimal weighting factors. The main advantage of this approach is its potentially higher performance. Therefore, it is proposed to select IRI signals with frequency hopping operating at common frequencies using their spatial parameters, for example, in the direction of their arrival (bearing θ). At present, spatial parameters meters are known (see Pat. RF No. 2341811, IPC G01S 3/14, publ. 12/20/2008; Pat. RF No. 2263327, IPC G01S 3/14, publ. 10/27/2005), allowing high accuracy to measure θ for various conditions with an error within two degrees. Therefore, when working with correspondents even in a limited sector, for example 80 °, the proposed device is able to select and simultaneously receive (with uniform dispersal of correspondents in azimuth) up to 40 IRI. The implementation of narrow-band reception (see ibid.) With respect to each of the signals given by the IRI provides an increase in its quality and efficiency. Due to the fact that the adaptation process is carried out in M narrow frequency bands f _i , M <N, the amount of interference radiation in each of them is much smaller. This allows you to reduce the requirements for the number of used antenna elements N. Ensuring the simultaneous and high-quality reception of signals of all IRI with frequency hopping at common frequencies required changes to the BCU 6, the block fixing the weight coefficients 4 and the block forming the weight coefficients 3. In this case, the most important device is saved the prototype characteristic is the rate of adaptation to the signal-noise environment.

, а при его включении - сигнальный

. Последние соответствуют амплитудам полезного сигнала и аддитивной смеси помех и шумов. Эти напряжения используют для формирования весовых коэффициентов в БФВК 3. Синтез W(f_i,θ_j) целесообразно осуществлять в районе использования устройства для получения максимальной априорной информации о сигнально-помеховой обстановке на частотах, используемых корреспондентами с ППРЧ. Направление прихода сигнала переносного генератора θ_j и частота f_i известны благодаря работе блока 5.A multi-channel adaptive radio receiving device (see figure 1) works as follows. At the preparatory stage, determine the reference values of the vector of weight coefficients W (f _i , θ _j ) for all frequencies f _i , i = 1, 2, ..., K of all directions θ _j , j = 1, 2, ..., J, used in the work J >> M, J> K. For the UHF band, the frequency resolution can be Δf = 25 kHz, and in the direction, for example, Δθ = 2 °. For this purpose, a remote generator at a distance of several wavelengths from the antenna array 2 emit harmonic signals in a given frequency band ΔF with discreteness Δf. An additive mixture of the generator signal, interference and noise from the output of the antenna elements 2 is fed to the inputs of the BVS1. Here, the received signals are weighted in the ΔF band (frequency hopping band) and their addition. Next, the total signal is fed to the input of the BCU 6, where they perform the selection of the signal of the external generator at frequencies f _i , i = 1, 2, ..., K, and the formation of quality indicators by diluting the input signal stream (due to a priori knowledge of the moments of switching on the generator). In the absence of a generator signal at a frequency f _i in the BCF 6 form an interference quality indicator

, and when turned on - signal

. The latter correspond to the amplitudes of the useful signal and the additive mixture of interference and noise. These voltages are used to form weight coefficients in BFVK 3. It is advisable to synthesize W (f _i , θ _j ) in the area of use of the device to obtain maximum a priori information about the signal-noise situation at the frequencies used by the frequency hoppers. The direction of arrival of the signal of the portable generator θ _j and the frequency f _{i are} known due to the operation of block 5.

, и минимизации помехового

. Вследствие этого осуществляется компенсация мешающих сигналов и согласованный прием излучений генератора гармонических сигналов на всех частотах ППРЧ в полосе ΔF при его местоположении в точке θ_j.The weights obtained in block 3 for each i-th frequency position of the IRI with frequency hopping are used in block 1 to maximize the values of the signal quality indicator

, and minimizing interference

. As a result, interference signals are compensated and the harmonics of the harmonic signal generator receive radiation at all frequencies of the frequency hopper in the ΔF band at its location at the point θ _j .

After the time interval Δt necessary to complete the adaptation process of the inventive device at all frequencies f _i , i = 1, 2, ..., K, the values of the vectors W (f _i , θ _j ) generated in block 3 enter the weight fixing block 4 and are stored at the addresses determined by the frequency ratings f _i and the location of the harmonic signal generator θ _j (in block 4, the latter are received by the group of address outputs of the BOPP 5).

Consistently with the given discreteness Δθ, the harmonic signal generator is moved relative to the antenna array 2. For each point θ _j , j = 0 ÷ 360 ° and all frequencies f _i , i = 1, 2, ..., K, using blocks 1, 2, 3 and 5, 6 form the values of the vectors W (f _i , θ _j ) for all used frequencies of IRI with frequency hopping f _i , i = 1, 2, ..., K; and all possible directions of arrival of signals θ _j , j = 1, 2, ..., J and remember them in block 4.

и номиналов частот, на которых выявлена их работа и сравнение в,

с заданными значениями θ_j, j=1, 2, …, M. По истечении времени Δτ на группе выходов блока 5 появляется текущая информация о параметрах f_i и θ_j M работающих ИРИ с ППРЧ, которая поступает на адресные входы блоков 4 и 6. В блоке 4 величины f_i и θ_j используют для нахождения ранее определенных на подготовительном этапе значений векторов весовых коэффициентов W(f_i,θ_j). Информация о сигнально-помеховой обстановке на соответствующих частотах f_i с учетом направления прихода полезных сигналов θ_j, содержащаяся в блоке 4, поступает в блок 3 в соответствии с кодами их адресов f_i и θ_j, формируемых на выходах блока 5. Одновременно значения f_i и θ_j используют в БЧВО 6 для селекции входного потока сигналов заданных ИРИ с ППРЧ (для сортировки сигналов по корреспондентам). Данную операцию осуществляют по значениям параметров θ_j, которые задаются в блоке 5 по второй установочной шине 9 перед началом работы устройства. В противном случае, если значения θ_j, j=1, 2, …, M, априорно неизвестны, эта операция выполняется методом перебора сигналов работающих ИРИ с ППРЧ и "сортировка" их по текущим значениям параметра

В результате этого на выходной шине 8 блока 6 появляются "собранные" на разных частотах отрезки излучений и рассортированные по M корреспондентам. Кроме того, БЧВО 6 формирует две группы показателей качества

и

, которые поступают на соответствующие входы БФВК 3. Эти напряжения используют в блоке 3 для уточнения весовых коэффициентов, поступивших с группы выходов блока 4 (по аналогичному алгоритму, реализованному в устройстве-прототипе). Отличие состоит в том, что на каждой частотной позиции ИРИ с ППРЧ осуществляется независимое уточнение весовых коэффициентов. Уточненные в блоке 3 значения W(f_i,θ_j) используют в блоке 1 для максимизации сигнальных показателей качества

и минимизации помеховых

. В результате достигается более быстрая (по сравнению с аналогами) и точная компенсация мешающих сигналов и согласованный прием сигналов заданных ИРИ. В процессе работы заявляемого устройства уточненные значения W(f_i,θ_j) с выхода блока 3 поступают в блок 4 и обновляют содержимое хранящейся информации о сигнально-помеховой обстановке по соответствующим адресам {f_i,θ_j}. Таким образом, заявленное устройство формирует такую диаграмму направленности в полосе ППРЧ ΔF, у которой минимумы соответствуют направлениям на источники помех, а максимумы ориентированы в направлении ИРИ с ППРЧ. В результате достигается многоканальный помехозащищенный прием сигналов M источников с ППРЧ.In the process of operation of the inventive device (see Fig. 1), an additive mixture of signals with frequency hopping, interference and noise from the output of the antenna array 2 is fed to the inputs of the BVS 1. In block 1, the received signals are weighted in the ΔF band and added. Then they follow in the BCCH 6. In block 6, the received signals are filtered out by K frequency channels and their delay is Δτ. The last operation is necessary to compensate for temporary losses in block 5 to determine at the current time the directions of arrival of the IRI signals

and the nominal frequencies at which their work and comparison in

with the given values θ _j , j = 1, 2, ..., M. After the time Δτ, the current information about the parameters f _i and θ _j M of the operating IRR with frequency hopping, which is received at the address inputs of blocks 4 and 6, appears on the group of outputs of block 5 In block 4, the values of f _i and θ _j are used to find the values of the vectors of weight coefficients W (f _i , θ _j ) previously determined at the preparatory stage. Information about the signal-noise situation at the corresponding frequencies f _i , taking into account the direction of arrival of the useful signals θ _j , contained in block 4, enters block 3 in accordance with the codes of their addresses f _i and θ _j generated at the outputs of block 5. Simultaneously, the values of f _i and θ _j are used in BCHVO 6 for selection of the input signal stream of the given IRI with frequency hopping (for sorting signals by correspondents). This operation is carried out according to the values of the parameters θ _j , which are set in block 5 by the second installation bus 9 before starting the operation of the device. Otherwise, if the values of θ _j , j = 1, 2, ..., M, are a priori unknown, this operation is performed by sorting the signals of working IRI with frequency hopping and “sorting” them by the current values of the parameter

As a result of this, on the output bus 8 of block 6, segments of radiation “collected” at different frequencies appear and sorted by M correspondents. In addition, the BSEC 6 forms two groups of quality indicators

and

which are supplied to the corresponding inputs of the BFVK 3. These voltages are used in block 3 to clarify the weight coefficients received from the group of outputs of block 4 (according to a similar algorithm implemented in the prototype device). The difference is that at each frequency position of the IRI with frequency hopping, an independent refinement of the weighting coefficients is carried out. The values W (f _i , θ _j ) specified in block 3 are used in block 1 to maximize signal quality indicators

and minimizing interference

. As a result, faster (in comparison with analogs) and accurate compensation of interfering signals and consistent reception of signals of specified IRI are achieved. During the operation of the inventive device, the updated values of W (f _i , θ _j ) from the output of block 3 go to block 4 and update the contents of the stored information about the signal-noise situation at the corresponding addresses {f _i , θ _j }. Thus, the claimed device generates such a radiation pattern in the frequency hopper band ΔF, in which the minima correspond to the directions to the sources of interference, and the maxima are oriented in the direction of the IRI with frequency hopping. As a result, multichannel noise-immune reception of signals of M sources with frequency hopping is achieved.

, где Δθ - величина, определяемая точностными характеристиками блока 5 и может составлять, например 1 или 2 градуса. По окончании работы ИРИ на i-й частоте в блоке 5 уточняются значения

. Однако резкие изменения пространственных параметров θ_j ИРИ с ППРЧ, вызванные их перемещениями между сеансами связи, приведут к проблемам, связанным со значительными временными затратами на процессы адаптации, и как следствие - к потерям передаваемой информации в начале сеанса связи.At the end of the work of the mth IRI at the frequency position f _{i, the} updated value of the vector of weight coefficients W (f _i , θ _j } _{m is} stored in block 4 at the corresponding {f _i , θ _j } address. In the next operation cycle of the nth IRI with The frequency hopping frequency at this i-th frequency will use the updated value of the vector W (f _i , θ _j } _m . In this case, the operation of the inventive device allows a gradual (smooth) change in the azimuthal parameter of the IRI signals with frequency hopping (caused, for example, by moving the latter). in this case, in block 5, the value of the spatial parameter θ _j m of IRI. This became possible due to the fact that the values of θ _j are set as

where Δθ is a value determined by the accuracy characteristics of block 5 and can be, for example, 1 or 2 degrees. Upon completion of the IRI at the i-th frequency, in block 5, the values are specified

. However, sharp changes in the spatial parameters θ _{j of} IRI with frequency hopping caused by their movements between communication sessions will lead to problems associated with significant time costs for adaptation processes, and as a result to loss of transmitted information at the beginning of a communication session.

The multi-channel adaptive radio receiving device remains operational even without a preparatory stage. In this case, at the initial broadcasting of the IRI with frequency hopping device, the device will require large time costs for adaptation processes. At high speeds changing operating frequencies, problems may arise with the use of the proposed device.

In the inventive device, the time spent on adaptation to open source software is similar to the cost of the prototype and is significantly lower than that of the known analogues. A positive effect on speed is achieved by taking into account a priori information about STRs at used frequencies at previous times (see Nikitchenko V.V., Smirnov P.L. Estimation of spatially polarized parameters of signals and noise when receiving radiation with pseudo-random tuning of the operating frequency .-- Radio engineering and electronics, 1990, t. 35, No. 4, p. 767-774).

и

. Здесь под априорным знанием значения параметра θ_j может также пониматься регулярность (стабильность) проявления азимутального угла θ_j излучения m-го ИРИ с ППРЧ на разных частотах в течении сеанса связи.The time-frequency processing unit 6 (see Fig. 1) is implemented as a K-channel receiving device. The receiving channels 12.1-12.K are tuned to the frequency positions of the signals from the PFTRCH. A priori knowledge of the directions of arrival of signals given by IRI with frequency hopping θ _j provides uninterrupted entry into communication with M correspondents and the formation of quality indicators

and

. Here, by a priori knowledge of the value of the parameter θ _{j, we} can also mean the regularity (stability) of the manifestation of the azimuthal angle θ _{j of the} radiation of the mth IRR with frequency hopping at different frequencies during the communication session.

The total signal from the output of block 1 is fed to the inputs of the receiving channels 12.1-12.K BSWO 6. Having passed through the bandpass filter 13, it is delayed by the time Δτ in the delay element 14. This operation is necessary to compensate for the time costs in block 5 for measuring the parameters f _i and θ _j and the implementation of the first stage of selection (determination of the belonging of the IRI signals with frequency hopping "friend or foe"). The values of the specified IRI {f _i , θ _j } measured in BOPP 5 are supplied to the inputs of the first code converter 11. The functions of block 11 include determining the number of the receiving channel 12.1-12.K (by the value of f _i ), the output of which will be connected in accordance with value θ _j to the corresponding signal adder 10.1-10.M (the second stage of selection). In addition, the code combination from the outputs of block 11 goes to the group of inputs of the second code converter 22 of the selected receive channel 12. The functions of block 22 include the formation of a control pulse at its output, which is fed to the second input of the RS flip-flop 17, translating it into a second stable state . As a result, a control signal is generated at its output at time t ₁ , which opens the key 15. The received signal of the m-th IRS with frequency hopping and delayed in block 14 passes through block 15 to the input of the first switch 16. In accordance with the code combination received at its address inputs from the output of block 11 (the task of the latter is to convert the azimuthal angle θ _j to the form necessary to control the first switch 16) the output of block 16 is connected to the corresponding signal adder 10.m. When the mth IRI switches to a different operating frequency, another receive channel 12 is connected to the work, and the signal from its output also goes to the mth signal adder 10.m due to the fact that its arrival direction θ _j remains the same.

(сигнальный показатель качества).In addition, the control signal generated at the output of the RS-flip-flop 17 at time t ₁ switches the second switch 19. As a result, the input signal of the receive channel 12 is detected in block 18 and then its envelope through the second switch 19 is fed to the output of block 6 as useful component of the signal

(signal quality indicator).

In most known systems with frequency hopping, the duration of radiation at the frequencies used is constant and a priori known. This made it possible to use the standby multivibrator 21 to return the RS flip-flop 17 to its original state. Using a pulse generated by block 22 at time t ₁ and arriving at the input of block 21, a control signal is generated in the last one, the duration of which coincides with the time spent by the IRR with frequency hopping in the frequency position. The pulse (corresponding to the trailing edge of this signal) generated by the block 20, the RS-trigger 17 is returned to its original state. As a result, the passage of signals through the key 15 is prohibited, and the second switch 19 is returned to its original state. The signals received at the input of the reception channel 12 begin to be perceived as interference. The signals detected in block 18 (their envelope) through the switch 19 are fed to the output of block 6 as an interference quality indicator

Figure 2 shows the structural diagram of the spatial parameter estimation unit 5. In addition, the antenna array 2 is directly involved in measuring the spatial parameters of the signals. A phase interferometer is implemented using blocks 2 and 5 (see Pat. RF No. 2283505, IPC 7 G01S 13 / 46, published on 09/10/2006, bull. No. 25; Pat. Of the Russian Federation No. 2263328, published on 05.24.2004, No. 30).

At the preparatory stage of a multi-channel adaptive radio receiving device, the reference values of the primary spatial information parameters (PPIP) Δφ _{l, h} (f _i ) are calculated for the average values of the operating frequencies of the IRI with frequency hopping f _i = Δf (2i-1) / 2. The value of Δf is determined by the minimum bandwidth of the receiving paths BOPP 5 and BSWO 6. For this, a preliminary description of the spatial characteristics of the antenna array 2 of the inventive device is carried out. For this purpose, the mutual distances between the antenna elements (AE) A _{l, h of the} array 2 are measured when they are placed on a horizontal plane. In the general case (Z _{l, h} ≠ 0), the distances between the projections of the spatial arrangement of the AE on the horizontal plane passing through the first element are used. In this case, for each AE, the values {Z _{l, h} } are additionally measured as {Z _{l, h} } = {Z _l } - {Z _h }. The measurement result for the first input mounting bus 7 (see Figs. 1 and 2) is input to the block for generating the reference values of PPIP 24. Here, according to the well-known algorithm (see Pat: RF 228505, IPC7 G01S 13/46, publ. September 10, 2006 G., bull. No. 25) calculate the values Δφ _{l, h, et} (f _i ), which are subsequently stored in the first storage device 25 (see figure 2). Introduced declination (if necessary) θ _flask antenna array 2 relative to the north direction, for example, as the angle between the vectors passing through the first and second AE and grating center toward the north.

In the process of operation of the inventive device using blocks 2, 26-36 (see figure 2), they search and detect PRI signals with frequency hopping in a given frequency band ΔF. The signals received by the antenna array 2 at a frequency f _i are supplied to the corresponding inputs of the antenna switch 26. The task of the latter is to provide synchronous connection in a single time interval of any AE pairs to the reference and signal outputs. As a result, the signals from all possible AEs of the grating 2 are received sequentially in time at both signal inputs of the two-channel receiver 27. Moreover, all AEs periodically act as both signal and reference ones (provided that the fully accessible switch 26 is used). This achieves the maximum set of statistics on the spatial parameters of the electromagnetic field.

The signals received at the inputs of the receiver 27 are amplified, filtered and transferred to an intermediate frequency, for example 10.7 MHz. From the reference and signal outputs of the intermediate frequency of block 27, the signals are supplied to the corresponding inputs of the two-channel block of analog-to-digital conversion (BACP) 28, where they are synchronously converted to digital form. In addition, the tuning frequency code f _{i of the} receiver 27 from its address output is supplied to the second group of inputs of the comparison unit 37.

The obtained digital samples of the AE signals A _l and A _h in block 28 are multiplied by digital samples of two harmonic signals of the same frequency, shifted relative to each other by π / 2. As a result, in block 28, four report sequences are generated (quadrature components of the signals from two AEs A _l and A _h ). To implement the necessary impulse response of the digital filters in block 28, the operation of multiplying each quadrature component of the signal by the corresponding samples of the time window is performed. The order of these operations is described in detail in Pat. RF No. 2263328 and Pat. RF №228505. At the final stage in block 30 form two complex sequence of samples.

получают две преобразованные последовательности, характеризующие спектры сигналов в АЭ A_l и A_h, а следовательно, и их фазовые характеристики. Измерение разности фаз Δφ_l,h(f_i) в парах A_l и A_h предполагает вычисление функции взаимной корреляции сигналов в соответствии с выражениемThe signals from the output of the BACP 28 are supplied to the corresponding inputs of the Fourier transform unit 29. As a result of the execution in block 29 of the operation in accordance with the expression

get two converted sequences characterizing the spectra of the signals in AE A _l and A _h , and therefore their phase characteristics. The measurement of the phase difference Δφ _{l, h} (f _i ) in pairs A _l and A _h involves the calculation of the cross-correlation function of the signals in accordance with the expression

,

,

where l, h = 1, 2, ..., N, l ≠ h is the AE number. Based on it, Δφ _{l, h} (f _i ) is defined as

.

.

This function is performed by block 30. The measured value Δφ _{l, h} (f _i ) is written into the second memory 31 by the next pulse of the generator 23. This operation is performed until the PPIP values for all possible combinations of AE pairs are written to these blocks. The execution of this operation corresponds to the formation of an array of measured PPIP Δφ _{l, h, ISM} (f _i ).

The main purpose of blocks 32, 33, 34, 35 and 24, 25 is to assess the degree of difference between the measured parameters Δφ _{l, h, ism} (f _i ) from the reference values measured for all directions of the signal Δθ _j and all frequencies Δf _j .

where J = 1, 2, ..., J; JΔθ = 360 °, i = 1, 2, ... I; IΔf = ΔF.

As a result, a data array H _θ (f _i ) is formed in the third storage device 35, based on which the desired parameter θ _{j is found} . This operation is carried out in block 36 by searching for the minimum sum H _θ (f _i ) in the data array H _θ (f _i ). The measurement results {f _i , θ _j } are input to the comparison unit 37.

с заданными значениями θ_j. При совпадении с одной из заданных величин

и соответствующее ему значение частоты f_i поступают на адресные входы блоков 4 и 6. Кроме того, в процессе измерения пространственного параметра

(см. фиг.3) осуществляют усреднение полученных оценок в

и уточнение заданного по шине 9 значения θ_j. При отсутствии исходной информации о направлениях на ИРИ с ППРЧ в блоке 37 осуществляется определение усредненных значений

на всех отмеченных в работе в полосе ΔF радиосредств, а значения {f_i,θ_j} поступают на входы блоков 4 и 6 в соответствии с рассмотренным алгоритмом.Before starting the operation of the device (see Fig. 8), the a priori known azimuths are entered into the block 37 via the first installation bus 9 for the given IRI with the frequency hopping θ _j , j = 1, 2, ..., M, which are stored in it. In the process of operation of the device, as the direction is measured for the next PRI in block 37, the found parameter is compared

with given values of θ _j . When coinciding with one of the given values

and the corresponding frequency value f _{i is} supplied to the address inputs of blocks 4 and 6. In addition, in the process of measuring the spatial parameter

(see figure 3) carry out the averaging of the obtained estimates in

and refinement of the value θ _j set on the bus 9. In the absence of initial information about directions to Iran with frequency hopping in block 37, the determination of averaged values

on all radio facilities noted in the work in the ΔF band, and the values {f _i , θ _j } are supplied to the inputs of blocks 4 and 6 in accordance with the considered algorithm.

It should be noted that BOPP 5 is able to measure the elevation angle β of the arrival of radio signals. However, in the proposed device for the selection of signals of various IRI with frequency hopping, only the value θ _{j is used} as the most informative parameter. The elevation angle β in most practical cases is close to zero and therefore uninformative. In addition, the accuracy of measuring the elevation angle β, as a rule, is lower than the accuracy of measuring the bearing θ _j due to the implementation features of the antenna arrays used.

As a criterion for making a decision on the selection of IRI signals with frequency hopping in the proposed device is the property of the approximate equality of the parameter θ _j for all frequencies used and all components of the spectrum of the signal from one source (see figure 3). In this case, the spread of the values of the bearing θ _j for various operating frequencies within small limits Δθ = 2-4 ° due to measurement errors due to a number of well-known reasons (see Fig. 3) is allowed. The noise and other emissions taking place are irregular in nature and do not affect the performance of the claimed device.

In the case of insufficient speed, BOPP 5 can be performed N-channel (in terms of AE number), for example, eight- or sixteen-channel. In this case, the need for an antenna switch 26 disappears, and the elements 27, 28, 29, 30, 31, 32 and 33 are N-channel.

The unit for fixing the weighting coefficients 4 (see Fig. 4) is intended for storing measured at the preparatory stage, as well as at the previous stages of the device operation, the values of the vectors of the weighting coefficients W {f _i , θ _j } for all used frequency positions f _i , i = 1, 2, ..., N and all possible directions θ _j , j = 1, 2, ..., J.

When detecting radiation of the mth IRI with frequency hopping at the i-th frequency, control information about the detection of a given IRI with parameters {f _i , θ _j } is received from the output of the comparison unit 37 of BOPP 5 (see FIG. 2). The named values are sent to the group of information inputs of the decoder 38. The purpose of block 38 is to convert the values of f _i and θ _j into a code combination of the address of the corresponding latch channel 39. As a result, an address of the memory array of block 40 is formed on one of the KJ groups of outputs of block 38 the corresponding fixation channel 39, which contains the value of the vector W {f _i , θ _j ) _m obtained by block 3 upon the output of the mth IRI at the i-th frequency in the previous operation cycle. At the same time, this output signal of block 38 is supplied to the group of inputs of the code converter 45 of the corresponding processing path 41. Block 45 converts the incoming input signal into a control pulse (first control signal). On the leading edge of this signal, the address (converted code of the tuning frequency of the mth IRI and the direction of its arrival) is recorded in block 40. On the trailing edge of this pulse, the contents of the memory block 40 located in it at this address are read. In addition, the same control pulse through the first delay element 49 is supplied to the corresponding input of the second adder 43.m and then, as an element of the first group of control signals of block 4, to the first group of control inputs of block 3. The delay time of the first control signal in block 49 corresponds to the time interval necessary for generating information from the memory block 40 (see figure 4) and its conversion in blocks 54 (see figure 6).

Thus, the contents of the memory block 40 (the value of the vector W {f _i , θ _j } _m ) follows the group of inputs of the block of elements And 50. At the same time, the control pulse from the output of block 45 affects the input of the pulse selector 46. The task of the latter is to generate the first output (on the leading edge) of a pulse of a duration that coincides with the duration of the radiation from an IRR with frequency hopping at the frequency position. This signal of block 46 allows the passage of the value W {f _i , θ _j } _m from the output of block 40 through the block of elements 50 to the corresponding input of the first adder 42.m and then to the second group of information inputs of block 3.

The second important function of block 46 is to block all processing paths 41 of the remaining latching channels 39 tuned to a given i-th frequency. The need for this is that the claimed device provided the adaptation process at each frequency from the set i = 1, 2, ..., M, to the signals of only one (the first one that came out on it) of the mth IRI with frequency hopping. Otherwise, simultaneous reception of signals from several IRIs is possible, which corresponds to their mutual suppression. In addition, the time-shifted appearance of the signals of several IRIs at the ith frequency (overlapping them) would require block 3 to constantly be in tuning mode at this frequency, which corresponds to an additional deterioration of the ratio η. In this regard, a blocking signal is generated at the second output of block 46, which is fed to the blocking inputs of other processing paths 41 tuned to a given frequency.

The task of block 47 includes generating a second control signal at the trailing edge of the pulse taken from the first output of block 46. The second control signal is supplied to the corresponding input of the third adder 44.m and then, as an element of the second group of control signals of block 4, to the second group of control inputs block 3. The second control signal delayed in block 48 is used to record the new value of the vector W {f _i , θ _j } _{m to the} original or specified address. The latter is set by block 5 through the decoder 38. The trailing edge of this signal nullifies the address register of block 40. Next, a new cycle of operation of block 4 follows.

и

. В противном случае при одновременном приеме сигналов нескольких ИРИ с ППРЧ показатели U_С и U_П будут постоянно изменяться, а блок 3 непрерывно находится в режиме адаптации. Каждый канал 51.1-51.K содержит первый сумматор 53 и N трактов адаптации 52A-52.N (см. фиг.6), которые в свою очередь состоят из цифроаналогового преобразователя 54, первого 55 и второго 58 ключей, второго сумматора 56, интегратора 59, генератора пертурбационной последовательности 60, умножителя 61 и аналого-цифрового преобразователя 57. Каналы 51.1-51.K идентичны между собой, поэтому работу блока 3 рассмотрим на примере одного из них.Block 3 (see FIGS. 5 and 6) is designed to generate such weighting factors that would ensure the formation of a radiation pattern with maxima in the direction of the given correspondents and minima in the direction of interfering signals and interference. Block 3 contains K channels for the formation of weight coefficients 51.1-51.K (according to the number of frequencies used by IRI with frequency hopping). This is due to the need to formulate quality indicators for each operating frequency.

and

. Otherwise, with the simultaneous reception of signals from several IRI with frequency hopping, the indicators U _C and U _P will constantly change, and block 3 is continuously in adaptation mode. Each channel 51.1-51.K contains the first adder 53 and N adaptation paths 52A-52.N (see Fig.6), which in turn consist of a digital-to-analog converter 54, the first 55 and second 58 keys, the second adder 56, the integrator 59, the generator of the perturbation sequence 60, the multiplier 61, and the analog-to-digital converter 57. The channels 51.1-51.K are identical to each other, so we will consider the operation of block 3 using one of them as an example.

Upon detection of signals of a given m-th IRI with frequency hopping at the first operating frequency f ₁ from the direction θ _j from the group of information outputs of block 4 (bl. 42.1), the weighting coefficients W ₁ (f ₁ , θ _j ), W ₂ (f ₁ , θ _j ), ..., W _N (f ₁ , θ _j ). These values were generated by block 3 and recorded in block 4 at the preparatory stage of the device or at the previous exit cycle of the mth IRI at the first frequency f ₁ and reflecting the STR at that time. In each adaptation path 52.1-52.N, the received weights are converted into analog form in blocks 54 and fed through the key 55 to the first input of the second adder 56. The passage of the weights through the keys 55 of all paths 52A-52.N is controlled by the first control signal received to the first control input of block 3 (block 51.1) from the first control output of block 4 (block 43.1). The duration of the first control signal is determined by the time necessary to complete the first stage of the formation of the next value of the vector W (f ₁ , θ _j ) in block 3 (block 52.1).

и

, соответствующие уровням сигналов заданного ИРИ с ППРЧ и помех на первой рабочей частоте. Результаты перемножения названных величин поступают на вход интегратора 59. Кроме того, пертурбационная последовательность с выхода генератора 60 поступает на второй вход второго сумматора 56, на первый вход которого подается напряжение с выхода интегратора 59. В результате в блоке 56 трактов 52 осуществляют уточнение предшествующей информации о СПО с помощью текущих показателей качества

и

. Изменяющиеся сигналы генератора 60 и интегратора 59 предназначены для определения отклонения текущего значения веса относительно оптимума. В результате выполняется сканирование комплексных весовых коэффициентов относительно среднего значения 〈W〉 на величину ΔW_n, n=1, 2, …, N. Такое сканирование необходимо для определения градиента ∇W. Таким образом, обеспечивают независимое приведение комплексных весовых коэффициентов к оптимуму.At the same time, the generator 60 generates a random sequence, which is fed to the first input of the multiplier 61. Voltage is applied to the second input of the block 61

and

corresponding to the signal levels of a given IRI with frequency hopping and interference at the first operating frequency. The results of the multiplication of these quantities are fed to the input of the integrator 59. In addition, the perturbation sequence from the output of the generator 60 is fed to the second input of the second adder 56, the first input of which is supplied with voltage from the output of the integrator 59. As a result, in the block 56 of paths 52, the previous information on Open source software with current quality indicators

and

. The changing signals of the generator 60 and integrator 59 are designed to determine the deviation of the current weight value relative to the optimum. As a result, scanning of complex weighting coefficients relative to the average value of 〉W〉 is performed by ΔW _n , n = 1, 2, ..., N. Such a scan is necessary to determine the gradient of ∇W. Thus, they provide independent reduction of complex weights to the optimum.

Accounting for the value of the vector of weight coefficients W (f ₁ , θ _j ), which characterizes the STR when the IRI comes out at the first frequency in the previous work cycle, is used only at the first, stage of formation of its next value. Next, the key 55 is closed and the unit 3 at the first frequency operates in the normal mode. Block 55 is locked due to the termination (end of pulse) of the first control signal of block 4.

With the next change in the mth IRI of the operating frequency, the second control signal of block 4 opens the key 58 of each path 52.1-52.N, and the voltages from the outputs of the integrators 59 (values of the elements of the vector of weight coefficients) go to the inputs of the analog-to-digital converters 57. Blocks 57 convert analog voltages in digital form, which then go to the group of information inputs of block 4 and are stored at {f ₁ , θ _j }. The function of the second control signal delayed in block 48 (see FIG. 4) for the time required to convert W (f ₁ , θ _j ) into digital form and write it to block 40 includes resetting the address register of block 40. After that the next cycle of block 3 begins.

The implementation of the proposed device does not cause difficulties. A multi-channel adaptive radio receiver device uses known elements and units described in the scientific and technical literature.

Implementation options for weighted addition 1 are widely considered in the literature (see Monzingo, R.A., Miller, T.U., Adaptive Antenna Arrays: Introduction to Theory. - M.: Radio and Communications, 1986, p. 488; P. Smirnov. Methods of spatial processing of radio signals (the use of adaptive antenna systems and frequency hopping signals). In the book Methods of spatial processing of radio signals. A manual edited by Komarovich VF - L .: VAS, 1989, pp. 27-32). In general, BVS1 contains N × K complex weight multipliers and a common adder. The latter can be made in the form of high-frequency transformers on coaxial or microstrip lines depending on the frequency range (see the Handbook of electronic devices: in 2 volumes. T.1 / Burin LI, Vasiliev VP, Koganov V . I. and others. - M .: Energy, 1978).

Implementation options for the antenna elements of array 2 are widely considered in the literature (see Saidov A.S. et al. Design of phase automatic direction finders. - M.: Radio and Communications, 1997; Torrieri DJ Principles of military communications system. Dedham. Massachusetts. Artech House , Inc., 1981. - 298 p). In the inventive device, the lattice 2 performs a dual function:

is an element of an adaptive antenna system (antenna array of a multichannel adaptive radio receiving device itself);

antenna system for the block for determining spatial parameters 5.

As antenna elements of array 2, it is advisable to use one of the well-known types: symmetric (asymmetric) vibrators, surround vibrators, discus antennas, biconical antenna elements, etc. The type of antenna elements and their dimensions are determined by the given frequency range ΔF, overlap coefficient, design features of the array . The number of antenna elements N used and the distance between them depends on the maximum possible number of simultaneously operating IRRs with frequency hopping, interference IRI, the range of operating frequencies ΔF, the effect of the mutual influence of the antenna elements on each other, the specified accuracy of measuring the spatial parameters of the signals (accuracy of selection of the input signal stream) and etc.

To ensure stable interference-free signal reception in a wide sector with approximately equal characteristics, it is preferable to use antenna array 2 with a ring (elliptical) arrangement of antenna elements (see Kukes I.S., Starik M.E. Fundamentals of radio direction finding. - M .; Sov. Radio , 1964 .-- 640 s.). To eliminate the mutual influence between blocks 2 and 5, it is advisable to put dividers, for example, LVS IP by LANS (see http://www.lans.spb.ru).

The implementation of the unit for the formation of weighting coefficients 3 is known and widely covered in the literature (see Monzingo, R.A., Miller, T.U., Adaptive Antenna Arrays: Introduction to Theory. - M.: Radio and Communication, 1986, p. 488). Block 3 can be performed by a set of N similar prototype blocks. Adders 53 and 56, integrators 59, multipliers 61 can be performed using differential amplifiers that implement the corresponding operations on the signals (see Red E. Reference manual on high-frequency circuitry: Circuits, blocks, 50 ohm technology: Translated from German - M .: Mir, 1990.256 s.). Block 54 can be implemented on chips 572PV1, analog-to-digital Converter 57 - on chips 572PAA.

The implementation of the side of the fixation of weights 4 is known and widely covered in the literature. The memory unit 40 can be made by a set of K memory chips, for example 132 series RU10 or RU20. The decoder 38 is implemented according to the well-known scheme (see the Handbook of Integrated Circuits / B.V. Tarabrin et al .; Edited by B.V. Tarabrin; 2nd ed. Revised ext. - M: Energy, 1980, Fig. .5-158, p. 683). The remaining elements are performed on the elementary logic of TTL-series (see ibid.).

The pulse selector 46 (see Fig. 7) is designed to generate at the first output (on the leading edge of the signal of block 45) a pulse of a duration that coincides with the duration of the IRR emission with frequency hopping at the frequency position. The second function of block 46 is to block all processing paths 41 of the remaining latch channels tuned to a given i-th frequency.

Block 46 contains the first element And 62, the pulse shaper 63, the second element And 64 and the element NOT 65. The selector 46 operates as follows. The leading edge of the signal of block 45, passing through the element And 62, starts the pulse shaper 63. The latter can be implemented using a standby multivibrator. Using block 63, a pulse of a given duration is generated, which, from the output of the selector 46, enters the inputs of the block of elements And 50, allowing the values W (f _i , θ _j ) to pass through them. In addition, the signal inverted in block 65 enters the inputs of the And elements 64 of the processing paths 41 of the other latching channels 39 tuned to this ith frequency, blocking them. As a result, the original path 41 is blocked. However, thanks to the block 63, in which the pulse of a given duration continues to form, the original path 41 continues to operate. The implementation of the elements of block 46 does not cause difficulties.

The implementation of the block for determining spatial parameters 5 is known and does not cause difficulties. Block 5 in conjunction with antenna array 2 implements a phase interferometer (see Pat. RF 2341811, IPC G01S 3/14, publ. 12/20/2008; Pat. RF 2263327, IPC G01S 3/14, publ. 10/27/2005 .). Blocks 26 through 39 are implemented similarly to the corresponding blocks of the above direction finders. Additionally, the value of its tuning frequency f _i is output from the radio receiver 27. When block 27 is implemented on ICOM IC-RS500 receivers, the REMOTE connector of one of them located on the rear panel removes the code combination in CI-V format about its tuning frequency (see ICOM IC-RS500 connected wide-range scanning receiver. Instruction Instruction / Firm "Sycom" - official authorized dealer of ICOM Inc. - M.:; tel./fax. (495) 332-1115, 124-4194, p. 15).

Блок 37 содержит первый блок памяти 66, M трактов сравнения 67.1-67.M и первый сумматор 68. Каждый тракт сравнения 67.i содержит второй сумматор 69, элемент сравнения 70, третий сумматор 71, делитель 72, счетчик импульсов 73, второй блок памяти 74 и формирователь импульсов 75.The comparison unit 37 (see Fig. 8) is designed to perform the first stage of selection of the input signal stream by spatial parameters. In addition, in the process of operation by block 37, the spatial parameters of the specified IRI are refined

Block 37 contains a first memory block 66, M comparison paths 67.1-67.M and a first adder 68. Each comparison path 67.i contains a second adder 69, a comparison element 70, a third adder 71, a divider 72, a pulse counter 73, a second memory block 74 and pulse shaper 75.

от истинного θ_j, например ±Δθ=2°. На каждой из M групп информационных выходов блока 66 присутствует одно заданное значение θ_m. В процессе работы измеренное значение θ_изм поступает на информационные входы второго блока памяти 74 и запоминается в нем. Блок 74 выполняет функцию буферного запоминающего устройства. Далее значение θ_изм поступает на вторую группу информационных входов блока 70, на первую группу входов которого поступает соответствующее тракту значение в θ_m с группы информационных выходов блока 66. В случае совпадения названных величин на выходе элемента сравнения 70 формируется управляющий импульс, который поступает на управляющие входы второго 69 и третьего 71 сумматоров. В результате разрешается прохождение значений θ_изм и

с выхода тракта 67 на вход сумматора 68. В функции блока 68, также как и блока 71, входит операция объединения информационных потоков θ_m и f_изм всех отмеченных в данный момент времени в работе заданных ИРИ с ППРЧ. Данная информация далее поступает на адресных входы блока 6, где осуществляется второй этап селекции входного потока сигналов и их расфильтровка по приемным каналам 12.1-12.K. Кроме того, значения {f_изм,θ_m} поступает на адресные входы блока 4, что позволяет использовать накопленную априорную информацию о СПО на предыдущих этапах работы. Задним фронтом управляющего сигнала блока 70 содержимое блока 74 обнуляется и тракт 67 готов к принятию очередного значения θ_изм.The operation of block 37 is as follows. At the preparatory stage of the device, on the second installation bus 9, the values of the spatial parameters M of the specified IRI with frequency hopping θ _m , m = 1, 2, ..., M are written to the first memory block 66. In the comparison element 70 of all paths 67.1-67.M, Δθ possible deviation of the measured value

from true θ _j , for example ± Δθ = 2 °. On each of the M groups of information outputs of block 66 there is one predetermined value θ _m . In the process, the measured value θ _{ISM is} supplied to the information inputs of the second memory block 74 and is stored in it. Block 74 performs the function of a buffer memory. Next, the value of θ _{ISM is} supplied to the second group of information inputs of block 70, the first group of inputs of which receives the value corresponding to the path in θ _m from the group of information outputs of block 66. If these values coincide, a control pulse is generated at the output of comparison element 70, which is fed to the control the inputs of the second 69 and third 71 adders. As a result, the passage of the values of θ _ism and

output from the path 67 to the input of the adder 68. In the function block 68, as well as block 71, includes a union operation information flow θ _m and f _edited all marked at a given time in a predetermined frequency hopping IRI. This information then goes to the address inputs of block 6, where the second stage of the selection of the input signal stream and their filtering by receiving channels 12.1-12.K are carried out. In addition, the values {f _meas , θ _m } are supplied to the address inputs of block 4, which allows using the accumulated a priori information about the STR in the previous stages of work. By the trailing edge of the control signal of block 70, the contents of block 74 are reset and path 67 is ready for the next value of θ _meas .

Using blocks 69, 72 and 73, an operation is performed to refine the current value θ of a given IRI. During the operation of the IRI at the frequency position, unit 5 manages to measure the parameter θ _ism several times (see Fig. 3). Moreover, the values of θ _ISM slightly differ from each other by Δθ _ISM for various reasons. In the pulse counter 73 accumulates the number of coincidence of the parameters θ _m and θ _ISM , and in block 69 - their accumulation. Using the divider 72 determine the adjusted value

которое и будет поступать на его выход. В каждом новом цикле работы эта величина уточняется.The function of block 75 includes the formation of a write pulse in block 66 of the value from the output of the divider 72 at the first mismatch of the values θ _m and θ _meas . In the further work of block 37, the specified direction to a given source is used

which will come to his exit. In each new work cycle, this value is specified.

The time-frequency processing unit 6 (see FIG. 1) contains well-known elements that are widely covered in the literature. Blocks 13-22 implement similarly to the existing blocks of the prototype device on elementary logic. Code Converter 11 performs the second stage of selection of the input signal stream. In accordance with the values θ _m , m = 1, 2, ..., M received at its input, block 11 generates commands for connecting the receiving channels 12.1-12.M to the corresponding signal adders 10.1-10.M. Block 11 is implemented as a code converter on elementary logic (see the Handbook of Integrated Circuits / B.V. Tarabrin, S.V. Yakubovsky and others - 2nd ed., Revised and additional - M .: Energy, 1980, fig. 5-158, p. 683). The remaining elements of block 6 are performed on the elementary logic of the TTL-series microcircuits (see ibid.).

Blocks 1, 3 and analog elements of block 6 can be implemented in digital form based on specialized digital signal processing modules (ADMDDC8WBL digital reception submodule installed on the AMBPCI basic module (see "Instrumentation Systems" www.insys.ru . Tel. (495) ) 781-27-50, fax (495) 781-27-51)).

Claims (2)

1. A multi-channel adaptive radio receiving device comprising a weighted addition unit, a time-frequency processing unit, the information input of which is connected to the information output of the weighted addition unit, and the group of information outputs is the device output bus, an antenna array made of N> 2 identical non-directional antenna elements the outputs of which are connected to the first group of information inputs of the weighted addition block, the block for generating weight coefficients, the first group of information outputs the dow of which is connected to the second group of information inputs of the weighted addition block, and the inputs for evaluating the useful and noise components of the signal are connected to the corresponding outputs of the useful and noise components of the signal of the time-frequency processing unit, a weight fixing block, the group of information inputs of which is connected to the second group of information outputs block for the formation of weight coefficients, the group of information inputs of which is connected to the group of information outputs of the block for fixing weight coefficients, and the first and second control inputs are connected respectively to the first and second control outputs of the block for fixing the weight coefficients, characterized in that an additional block for estimating spatial parameters is introduced, the first group of information inputs of which are combined with the first group of information inputs of the weighted addition block, the group of address outputs is connected to a group of address inputs of a time-frequency processing unit and a group of address inputs of a block for fixing weight coefficients, the first and second Paradise K-channel groups of control outputs which are connected respectively to the first and second K-channel groups of control inputs of the weighting unit, where K is the number of receiving channels of the time-frequency processing block, K >> 1, and the second and third groups of information inputs of the block estimates of spatial parameters are the first and second input installation buses of the device, respectively, and the time-frequency processing unit is made up of M signal adders, M> 1, the outputs of which are a group information outputs of the block, the first code converter, the group of information inputs of which is a group of address inputs of the block, and K receiving channels, K> M, the information inputs of which are combined and are the information input of the time-frequency processing block, M signal outputs of each of the receiving channels are connected to the corresponding inputs M of the signal adders, the outputs of the useful component of the signal K of the receiving channels are a group of outputs of the useful component of the signal of the block, the outputs of the interference component K of the receiving nth channels are the group of outputs of the noise component of the block signal, the groups of address inputs K of the receiving channels are bitwise combined and connected to the group of outputs of the first, code converter, each receiving channel contains a series-pass bandpass filter, a delay element, a key, and a first switch, M outputs of which are the information outputs of the receiving channel, and the input of the bandpass filter is the information input of the receiving channel, the second switch, the amplitude detector and RS-trigger, the output of which is is dined with the control inputs of the key and the second switch, the first output of which is the output of the useful component of the channel signal, the second output is the interference component of the channel signal, and the information input of the second switch is connected to the output of the amplitude detector, the input of which is connected to the output of the bandpass filter, pulse shaper connected in series waiting multivibrator, the second code converter, the group of address inputs of which is combined with the group of address inputs of the first switch and is the address ith group of inputs of the receiving channel, and the output of the pulse shaper is connected to the second input of the RS-trigger, the first input of which is connected to the output of the second code converter. 2. The device according to claim 1, characterized in that the unit for fixing the weight coefficients is made up of a decoder, J fixation channels, J> K, K first adders, K second adders and K third adders, and the group of information inputs of the decoder is a group of address inputs of the block , a KJ groups of outputs to sets of K groups are connected to the corresponding K groups of address inputs of J channels of fixation, K groups of information outputs of each of which are connected to the corresponding groups of information inputs K of the first adders, groups of inf the formation outputs of which are a group of information outputs of the block, and the KJ groups of information inputs of all J fixation channels are a group of information inputs of the block, K outputs of the first control signal of each fixation channel are connected to the corresponding inputs K of the second adders, the outputs of which are the first group of control signals of the block, K the outputs of the second control signal of each latch channel are connected to the corresponding inputs K of the third adders, the outputs of which are the second group of control block signals, and each latch channel contains a memory block and K processing paths, with K groups of address inputs of the memory block combined with groups of address inputs of the corresponding processing paths and at the same time K groups of address inputs of the channel, K groups of information outputs of the memory block connected to groups of information inputs corresponding processing paths, the first control outputs of which are connected to the corresponding first control inputs of the memory unit, the second control inputs of which are connected to the second control paths of the respective processing paths, the group of information outputs of the processing paths are a group of channel information outputs, the third control path output outputs are a group of outputs of the first channel control signal, and the fourth processing path control outputs are a group of outputs of the second channel control signal, K-1 blocking channel inputs connected to the blocking outputs of the corresponding paths of the K-1 channels, and the blocking output is connected to the blocking inputs of the corresponding path in K-1 channels, each processing path contains a series-connected code converter, pulse selector and block of AND elements, the group of inputs of which is a group of information inputs of the path, and the group of information outputs is a group of information outputs of the path, the group of inputs of the code converter is an address group the path, and the output is the first output of the path control, the pulse shaper, the first and second delay elements, the output of which is the second output of the path control, and the input is connected to the output the pulse shaper house is the fourth output of the path control, the input of the first delay element is connected to the output of the code converter, and the output of the first delay element is the third output of the path control, K-1 control inputs of the pulse selector are K-1 blocking inputs of the path, the second output of the pulse selector is the blocking output of the path, and the first output of the pulse selector is connected to the input of the pulse shaper.

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