RU2361225C1 - Device for determining frequency, type of modulation and keying of received signals - Google Patents

Abstract

FIELD: physics; radio.

SUBSTANCE: proposed device relates to radio electronics and can be used for determining carrier frequency, type of modulation and keying of signals, received in a given frequency range. The device contains a receiving antenna 1, input circuit 2, search unit 3, high-frequency amplifier 4, heterodyne 5, mixer 6, intermediate frequency amplifier 7, detector 8, video amplifier 9, device for creating frequency sweep 10, cathode ray tube 11, first 12, second 24 and third 46 switches, first 13, second 28, third 29, fourth 31 and fifth 33 amplitude detectors, first 14, second 27 and third 32 high-pass filters, first 15, second 19 and third 26 low-pass filters, first 16 and second 20 squaring devices, first 17 and second 22 voltage dividers, frequency detector 18, first 21, second 50, third 51 and fourth 52 spectrum analysers, first 23, second 30, third 34, fifth 54 and sixth 55 comparator units, phase detector 25, complex spectrum analyser 35, phase spectrum linear component analyser 36, amplitude spectrum symmetry analyser 37, first 38, second 39, third 56, fourth 57 and fifth 58 analogue-to-number converters, first 40, second 42, third 44, fourth 61, fifth 62 and sixth 63 AND matching elements, number-to-voltage converter 45, two-time phase multiplier 47, four-time multiplier 48, and eight-time multiplier 49.

EFFECT: increased functional capabilities of the device through determination of the order of phase keying of the received signal.

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Description

The proposed device relates to the field of electronics and can be used to determine the carrier frequency, the type of modulation and manipulation of signals received in a given frequency range.

Known methods and devices for determining the frequency, type of modulation and manipulation of received signals (USSR copyright certificates No. 524138, 620907, 868614, 1000930, 1012152, 1180804, 1187095, 1272266, 1290192, 1354124, RF patents No. 2124216, 2230330, 2276375, US patent No. 4443801, Vakin SA, Shustov LN Fundamentals of radio countermeasures and electronic intelligence. M: Sov. radio, 1968, p. 386-396, Fig. 10.3 and others).

Of the known devices, the closest to the proposed one is a device for implementing the "Method for determining the frequency" (RF patent No. 2276375, G01R 25/00, 2004), which is selected as the base object.

The specified device provides a search for signals in a given frequency range by tuning the superheterodyne receiver, generating a frequency sweep on the screen of a cathode ray tube (CRT), converting the frequency of the received signal, amplifying it by voltage, detecting and applying to the vertically-deflecting CRT plates. As a result, a pulse is generated on the screen, by the position of which the carrier frequency of the received signal is determined on the frequency sweep. After that, the type of modulation (amplitude or angular, phase or frequency) or manipulation (amplitude, frequency or phase) of the received signal is sequentially determined.

One of the characteristic features of modern and promising electronic means (RES) is the widespread use of complex signals with multiple phase shift keying.

Currently, there are a large number of codes used for phase manipulation (Barker, Gaimuller, Velty, Golei, Huffman, Frenz and others).

Moreover, on one carrier frequency when using phase-shift keying, you can send messages from one, two, three, and so on sources, achieving a significant increase in the speed of information transfer in the communication channel.

]. Для передачи сообщений от четырех источников используется восьмикратная фазовая манипуляция [ФМн-8,

].If discrete information is transmitted from a single message source on a single carrier frequency, then it is advisable to use double (binary) phase shift keying [FMN-2, φ _k (t) = {0, π}]. To transmit messages from two sources, four-fold phase-shift keying is used [FMn-4,

]. To transmit messages from four sources, eight-fold phase-shift keying is used [FMn-8,

].

In the general case, messages from m sources can be transmitted simultaneously on one carrier frequency using m-fold phase shift keying.

However, two-, four- and eight-fold phase manipulations, which have found wide application in practice, are advisable. A further increase in the multiplicity of phase manipulation is limited by the fact that the distance between the elementary signals is reduced and the noise immunity of the communication channel is substantially reduced.

The known device does not allow to determine the multiplicity of phase manipulation of the received signal.

An object of the invention is to expand the functionality of the device by determining the multiplicity of phase manipulation of the received signal.

The problem is solved in that a device for determining the frequency, type of modulation and manipulation of the received signals, containing in accordance with the closest analogue a series-connected receiving antenna, input circuit, high-frequency amplifier, mixer, the second input of which is connected to the local oscillator output, an intermediate frequency amplifier, a detector, a video amplifier and vertically-deflecting plates of a cathode ray tube, the horizontally-deflecting plates of which are connected to the output of the frequency the second scan, connected in series to the output of the high-frequency amplifier, the first key, the second input of which is connected to the output of the detector, the first amplitude detector, the first high-pass filter, the first quadrator, the first voltage divider, the second input of which is connected through the first low-pass filter to the output of the first an amplitude detector, a first comparison unit, the two outputs of which are the first and second outputs of the device, a frequency detector, a second low-pass filter, and a second oh quadrator and a second voltage divider, the second input of which is connected through the first spectrum analyzer to the output of the first key, and the output is connected to the second input of the first comparison unit, the second key is connected in series to the output of the first key, the second input of which is connected to the second output of the device, phase detector , a third low-pass filter, a second amplitude detector and a second comparison unit, the second input of which is connected in series through a second high-pass filter and a third amplitude detector the output of the phase detector, and the two outputs are the third and fourth outputs of the device, sequentially connected to the output of the frequency detector, a third high-pass filter, a fifth amplitude detector and a third comparison unit, the second input of which is connected through the fourth amplitude detector to the output of the second low-pass filter, and two the outputs are the fifth and sixth outputs of the device, the complex spectrum analyzer, the linear phase analyzer of the phase spectrum, the first pre the analog-code browser and the first coincidence element AND, the second input of which is connected through the series-connected symmetry analyzer of the amplitude spectrum and the second analog-code converter to the second output of the complex spectrum analyzer, and the output is the seventh output of the device, connected in series to the output of the second analog-code converter the first inverter and the second coincidence element AND, the second input of which is connected to the output of the first converter analog-code, and the output is the eighth output of the device, after the second inverter and the third coincidence element And, the second input of which is connected to the output of the first inverter and the output is the ninth output of the device, are connected to the output of the first converter analogously, it differs from the closest analogue in that it is equipped with a code-voltage converter, a third key, the third and fourth inverters and three processing channels, each of which consists of a series-connected phase multiplier, a spectrum analyzer, a comparison unit, the second input of which is connected to the output of of a spectrum analyzer, an analog-to-code converter, and an AND element, and a code-voltage converter, a third key, the second input of which is connected to the output of the first key and three processing channels, the second input of the matching element And the first processing channel is connected to the ninth output of the device with the converter output, the analog-code of the second processing channel, and the output is the tenth output of the device, the second input of the coincidence element And the second processing channel through the third inverter is connected to the output the converter is the analog-code of the first processing channel, and the output is the eleventh output of the device, the second input of the coincidence element And the third processing channel is connected through the fourth inverter to the output of the analog-code converter of the second processing channel, and the output is the twelfth output of the device, the phase is multiplied in the first processing channel twice, in the second - four times and in the third - eight times.

The structural diagram of the proposed device is presented in figure 1. Timing diagrams illustrating signals with amplitude, frequency and phase shift keying are shown in FIG. The space of signs of recognition of these signals is shown in Fig.3.

The device comprises serially connected receiving antenna 1, input circuit 2, high-frequency amplifier 4, mixer 6, the second input of which is connected to the output of local oscillator 5, intermediate-frequency amplifier 7, detector 8, video amplifier 9, and vertical-deflecting plates of a cathode ray tube (CRT) ) 11, the horizontally-deflecting plates of which are connected to the device 10 for forming a frequency sweep. The control inputs of the input circuit 2, the high-frequency amplifier 4, the local oscillator 5 and the frequency sweep forming device 10 are connected to the corresponding outputs of the search unit 3, for which a sawtooth voltage generator or an electric motor can be used. To the output of the high-frequency amplifier 4, a key 12 is connected in series, the second input of which is connected to the output of the detector 8, the amplitude detector 13, the high-pass filter 14, the first quadrator 16, the first voltage divider 17, the second input of which is connected to the output through the first low-pass filter 15 an amplitude detector 13, and a first comparison unit 23, the two outputs of which are the outputs of the device. A frequency detector 18, a second low-pass filter 19, a second quadrator 20 and a second voltage divider 22 are serially connected to the output of the key 12, the second input of which is connected through the spectrum analyzer 21 to the output of the key 12, and the output is connected to the second input of the first comparison unit 23. To the output of the key 12, a key 24 is connected in series, the second input of which is connected to the second output of the first comparison unit 23, a phase detector 25, a third low-pass filter 26, a second amplitude detector 28 and a second comparison unit 30, the second input of which is connected through a second filter 27 high frequencies and the third amplitude detector 29 is connected to the output of the phase detector 25, and the two outputs are the outputs of the device. A third high-pass filter 32, a fifth amplitude detector 33 and a third comparison unit 34 are connected to the output of the frequency detector 18 in series, the second input of which is connected to the output of the low-pass filter 19 through the fourth amplitude detector 31, and two outputs are outputs of the device. The complex spectrum analyzer 35, the analyzer 36 of the linear term of the phase spectrum, the first converter 38 are an analog code and the first coincidence element AND 40, the output voltage of which is a sign of the frequency shift keying (FMN) of the received signal. To the second output of the complex spectrum analyzer 35, an amplitude spectrum symmetry analyzer 37 and a second analog-code converter 39 are connected in series, the output of which is connected to the second input of the first coincidence element AND 40. A second coincidence element 42 is connected to the output of the first converter 38 analog-code, the second input which through the first inverter 41 is connected to the output of the second converter 39 analog-code, and the output voltage is a sign of amplitude manipulation (AMN) of the received signal. The second inverter 43 and the third coincidence element AND 44, the second input of which is connected to the output of the first inverter 41, are connected to the output of the first converter 38 analog-code, and the output voltage is a sign of phase shift keying (PSK) of the received signal. A digital-to-voltage converter 45, a key 46, the second input of which is connected to the output of the key 12, and three processing channels, each of which consists of series-connected phase multiplier 47 (48, 49), a spectrum analyzer 50, are connected in series to the output of coincidence element AND 44 (51, 52), comparison unit 53 (54, 55), the second input of which is connected to the output of the spectrum analyzer 21, an analog-to-code converter 56 (57, 58), and I 61 (62, 63) matching element. The second input of the first coincidence element AND 61 is connected to the output of the converter 57 analog-code of the second processing channel. The second input of the element of coincidence And 62 through the inverter 59 is connected to the output of the Converter 56 analog code of the first processing channel. The second input of the element of coincidence And 63 through the inverter 60 is connected to the output of the Converter 57 analog code of the second processing channel.

Moreover, in the multiplier 47 of the first processing channel, the phase is multiplied by a factor of two, in the multiplier 48, the phase is multiplied by four times, and in the multiplier 49, the phase is multiplied by eight.

The appearance of a logical unit at the output of the AND 61 coincidence element indicates a two-phase phase manipulation of the received signal. The appearance of a logical unit at the output of the second element of coincidence AND 62 indicates a four-fold phase manipulation. The appearance of a logical unit at the output of the AND 63 coincidence element indicates an eight-fold phase manipulation of the received signal.

The proposed device operates as follows.

The search for signals in a given frequency range Df is carried out using a search unit 3, which, according to a sawtooth law, consistently changes the settings of the input circuit 2, high-frequency amplifier 4 and local oscillator 5. At the same time, the search unit 3 controls the frequency sweep generation device 10 on the cathode ray tube screen 11 .

The received signal after frequency conversion in the mixer 6 and amplification in the intermediate frequency amplifier 7, detection in the detector 8 and additional amplification in the video amplifier 9 is supplied to the vertical-deflecting plates of the CRT 11, as a result of which a pulse (frequency mark) is formed on the screen, the position of which on a frequency sweep determines the carrier frequency of the received signal.

Modulated oscillation in the most general form can be written:

Here ω _c , φ (f) is the carrier frequency and phase of the oscillation;

φ (t) = ∫ω (t) dt + ϕ (t) + φ _с is the oscillation phase;

U (t) = U _c [1 + m · sinΩt] - envelope of the oscillation;

where U _with - the amplitude of the carrier in the absence of modulation;

m is the coefficient of amplitude modulation;

Ω is the frequency of the modulating function.

For a signal with amplitude modulation (AM), expression (1) will look like:

If the AM signal is fed to the input of the amplitude detector 13 from the output of the high-frequency amplifier 4 through the public key 12, then a voltage is generated at its output:

Therefore, at the output of the amplitude detector 13, when an AM signal is exposed to its input, a modulating function is allocated in which useful information is stored.

If the input of the amplitude detector 13 receives a signal with angular modulation (UM), then U (t) = U _c = const and expression (1) takes the form:

those.

It can be seen from the obtained expressions that in the absence of a parasitic PA with amplitude modulation of the oscillation and parasitic AM with angular modulation of the oscillation, it is possible to distinguish the amplitude-modulated signal from the signal with angular modulation by passing it through the amplitude detector 13.

The following parameters can be used as informative signs of recognition of signals with amplitude and angular modulations:

- effective coefficient of amplitude modulation

- среднеквадратическое значение переменного напряжения сигнала и шума на нагрузке амплитудного детектора 13;Where

- the rms value of the alternating voltage of the signal and noise at the load of the amplitude detector 13;

M (t) = ΔU (t) · sinΩt is the modulating function;

- effective frequency deviation

where T is the duration of the signal;

- spectrum width Δω _{c of the} received signal.

For the AM signal, these signs are equal to:

;m _eff = 0;

;

K ₀ ≅1 ÷ 1.5; m ₀ ≅2-3.

For the UM signal:

.m _eff ≥m ₀ ;

.

The effective amplitude modulation coefficient m _eff is determined using an amplitude detector 13, a high-pass filter 14, a low-pass filter 15, a quadrator 16, and a voltage divider 17.

The effective frequency deviation Δω _∂ef is determined using a frequency detector 18, a low-pass filter 19, a second quadrator 20 and a second voltage divider 22.

The width of the amplitude spectrum Δω _{c of the} received signal is determined using the spectrum analyzer 21.

The ratio Δω _c / Δω _∂ef is determined in the voltage divider 22. In the first comparison block 23, the measured values of m _eff and Δω _c / Δω _{∂ef are} compared with certain numerical values of m ₀ and K ₀ . The comparison results determine the type of modulation (amplitude or angular) of the received signal.

If the received signal has angular modulation, then a constant voltage from the second output of the comparison unit 23 is supplied to the control input of the key 24, opening it. In the initial state, keys 12 and 24 are always closed. In this case, the received signal with angular modulation from the output of the high-frequency amplifier 4 through the public keys 12 and 24 is received for further processing.

It should be noted that the recognition of the type of angular (frequency or phase) modulation is a complex technical task. This is due to the difficulty of identifying informative features by which it is possible to distinguish a signal with frequency modulation (FM) from a signal with phase modulation (FM), since frequency and phase modulations, due to the integro-differential coupling between the frequency and phase, the oscillations have much in common with each other, which justifies the existence of the combined term "angular modulation". Note that due to this connection, frequency modulation is always accompanied by a change in the phase of the modulated oscillation, and when phase modulation is performed, there is always a change in the frequency of the radio signal. These changes are inextricably linked with each other and the whole thing is which of them is primary, i.e. which one is proportional to the modulating function. With frequency modulation, obviously, the primary is the change in frequency, and with phase modulation is the change in the phase of high-frequency oscillations.

It should be noted that the recognition of FM and FM signals with a harmonic modulating function is generally impossible. However, real oscillations have a modulating function much more complex than harmonic. Therefore, there is a certain opportunity for the recognition of FM and FM signals using, as a sign of recognition, the deformation of the modulating function at the output of the frequency 18 and phase 25 detectors.

Let the expansion of the modulating function in a Fourier series on a certain time interval have the following form:

where U _i , Ω _i , φ _i - amplitude, frequency and initial phase of the i-th spectral component.

It is known that at the output of the phase detector 25, the oscillation phase will be distinguished:

and at the output of the frequency detector 18, the differential from the phase is obtained:

Consider the case when the type of detector corresponds to the type of angular modulation of the received signal.

For FM ω (t) = M (t), ϕ (t) = 0 and at the output of the frequency detector 18 we will have:

When FM ω (t) = 0, ϕ (t) = M (t) and at the output of the phase detector 25 we will have:

If the type of detector does not match the type of angular modulation, then the following situations are possible.

Let the FM signal be input to the phase detector 25. Moreover, ω (t) = M (t), ϕ (t) = 0 and at the output of the phase detector 25 we will have:

Analyzing formula (11), we see that the spectrum of FM vibrations after phase detector 25 undergoes deformation. With increasing number of the spectral component, its amplitude will decrease, i.e. the ratio of the amplitudes of the spectral components taken at the beginning of the frequency axis to the amplitude of the spectral components taken at a certain distance from the beginning of the axis will be more than 1.

Now we consider the FM-oscillation path through the frequency detector 18.

For FM, ω (t) = 0, ϕ (t) = M (t) and at the output of the frequency detector 18 we will have:

From formula (12) it is seen that the spectrum of the FM vibration at the output of the frequency detector 18 also undergoes deformation. With an increase in the number of the spectral component, its amplitude will increase, i.e. the ratio of the amplitudes of the spectral components taken at the beginning of the frequency axis to the amplitudes of the spectral components taken at a certain distance from the beginning of the axis will be less than 1.

The received UM signal from the output of the high-frequency amplifier 4 through the public keys 12 and 24 is fed to the inputs of the frequency 18 and phase 25 detectors. Low-pass filters 19 and 26 emit spectral components located at the beginning of the frequency axis. High-pass filters 27 and 32 emit spectral components located at some distance from the beginning of the axis. Amplitude detectors 28, 29, 31, and 33 extract the envelopes of the corresponding spectral components. Blocks 30 and 34 of the comparison determine the ratio of the amplitudes of the spectral components taken at the beginning of the frequency axis to the amplitudes of the spectral components taken at a certain distance from the beginning of the frequency axis, at the outputs of the phase 25 and frequency 18 detectors. Depending on the indicated relationship, a decision is made on the form of the angular (frequency or phase) modulation of the received signal.

If the specified ratio is greater than unity at the output of the phase detector 25, and the indicated ratio is approximately equal to unity at the output of the frequency detector 18, then the received signal has frequency modulation.

If at the output of the frequency detector 18 the ratio of the amplitudes of the spectral components taken at the beginning of the frequency axis to the amplitudes of the spectral components taken at a certain distance from the beginning of the frequency axis is less than unity, and at the output of the phase detector 25 this ratio is approximately equal to unity, then the received signal has phase modulation.

When manipulating high-frequency oscillations in amplitude, frequency and phase with the modulating function M (t) (bipolar DC packets), the manipulated signals will have the form shown in FIG. 2.

To recognize these signals, you can use the spectral method, which is based on the characteristics of the amplitude and phase spectra of amplitude-manipulated (AMn), frequency-manipulated (FMN) and phase-shifted (FMN) signals obtained in real time. Moreover, symmetry of the amplitude spectrum and the presence of a linear phase term are used as signs of recognition of these signals. In frequency manipulation, the amplitude spectrum does not have the symmetry property, while in amplitude and phase manipulation it is an evenly symmetric function of frequency. Denoting this feature by α, we obtain

α _AMn = 0, α _FMN = 0, α _FMN = 0.

On this basis, two classes of signals can be distinguished:

FSK signals and AMN (PSK) signals.

The phase spectra of AMn and FMN signals are characterized by the presence of a linear term.

Denoting this sign by β, we obtain

β _AMn = 0, β _FMN = 1, β _FMN = 0.

On this basis, it is possible to distinguish AMn, FMN signals from the FMN signal.

It should be noted that in the space of the indicated features, the considered signal classes do not intersect, i.e. their recognition can be performed with high reliability (figure 3).

The received manipulated signal from the output of the high-frequency amplifier 4 through the public key 12 is fed to the input of the complex spectrum analyzer 35, and then to the inputs of the linear term analyzer 36, phase term, and amplitude spectrum symmetry analyzer 37. The measured recognition features are fed to the inputs of the analog and code converters 38 and 39, where they are converted to digital codes, which enter the logical processing unit, consisting of coincidence elements AND 40, 42, 44 and inverters 41 and 43. The appearance of voltages at the outputs of the coincidence elements And 40, 42, 44 indicates frequency, amplitude and phase manipulation, respectively.

If the input of the panoramic receiver receives a complex signal with double phase shift keying

u _c (t) = U _c · cos [ω _c t + φ _k (t) + φ _c ], 0≤t≤T _c ,

where φ _k (t) = {0, π} is the manipulated component of the phase, which reflects the law of phase manipulation in accordance with the modulating code M (t), and φ _k (t) = const for kτ _e <t <(k + 1) τ _e and can change abruptly at t = kτ _e , i.e. at the borders between elementary premises (k = 1, 2, ..., N);

τ _e , N - the duration and number of chips that make up the signal of duration T _c (T _c = N · τ _e ),

then a logical unit is formed at the output of the AND element 44. This unit is converted in the code-voltage converter 45 to a constant voltage, which is supplied to the control input of the key 46 and opens it. In the initial state, key 46 is always closed.

In this case, the received signal U _c (t) from the output of the high-frequency amplifier 4 through the public key 12 and 46 is fed to the inputs of the three processing channels.

In this case, at the output of phase multipliers by two 47, four 48 and eight 49, the following harmonic oscillations are formed, respectively:

since 2φ _k (t) = {0.2π}, 4φ _k (t) = {0.4π}, 8φ _k (t) = {0.8π}, phase manipulation is already absent in the indicated oscillations.

,

,

), тогда как ширина спектра ФМн-сигнала определяется длительностью элементарных посылок

, т.е. ширина спектра указанных гармоник сигнала в N раз меньше ширины сигнала входного сигнала:The width of the spectrum of the second Δf ₂ , the fourth Δf ₄ and the eighth Δf ₈ harmonics of the signal is determined by its duration (

,

,

), while the spectrum width of the QPSK signal is determined by the duration of the elementary premises

, i.e. the spectrum width of the indicated harmonics of the signal is N times smaller than the width of the signal of the input signal:

The spectrum width Δf _{c of the} input QPSK signal Uc (t) is measured using a spectrum analyzer 21. The spectrum width of the second Δf ₂ , fourth Δf ₄ and eighth Δf ₈ signal harmonics is measured by spectrum analyzers 50, 51 and 52, respectively. Voltages U ₂ , U ₄ , U ₈ proportional to Δf ₂ , Δf ₄ , Δf _8, respectively, from the outputs of the spectrum analyzers 50, 51 and 52 are supplied to the first inputs of comparison blocks 53, 54 and 55, the second inputs of which are supplied with voltage U _c from the output of the spectrum analyzer 21, in proportion to U ₁ . Since U ₁ >> U ₂ , U ₁ >> U ₄ , U ₁ >> U ₈ , then positive voltages are generated at the output of comparison blocks 53, 54 and 55, which are supplied through the corresponding analog-code converters 56, 57 and 58 to the first inputs of the matching elements And 61, 62 and 63. The logical unit from the output of the second converter analog-code 57 is fed to the second input of the matching element And 61. The second input of the matching element And 62 through the inverter 59 is connected to the output of the analog-code 56 converter of the first channel processing. The second input of the coincidence element AND 63 through the inverter 40 is connected to the output of the analog-code converter 57 of the second processing channel.

Therefore, with a two-phase phase manipulation [φ _k (t) = [0, π}], a logical unit is formed only at the output of the AND 61 coincidence element.

, то на выходе умножителя 47 фазы на два образуется ФМн-2 сигнал [2φ_k(t)={0, π, 2π, 3π}], а на выходах умножителей фазы на четыре 48 и восемь 49 образуются гармонические колебания U₂(t) и U₃(t) соответственно, т.е. во втором и третьем каналах осуществляется свертка спектра принимаемого ФМн-сигнала. В этом случае в блоке 53 сравнения отношение U₁/U₂≈1 и на его выходе не формируется напряжение, т.е. образуется логический нуль. Логическая единица формируется на выходе элемента совпадения И 62, что является признаком распознавания ФМн-4 сигнала.If a signal with four-fold phase shift keying FMn-4 is input to the panoramic receiver

then, at the output of the phase 47 multiplier by two, an FMN-2 signal is generated [2φ _k (t) = {0, π, 2π, 3π}], and at the outputs of the phase multipliers by four 48 and eight 49 harmonic oscillations U ₂ (t ) and U ₃ (t), respectively, i.e. in the second and third channels, the spectrum of the received QPSK signal is convolved. In this case, in the comparison block 53, the ratio U ₁ / U ₂ ≈ 1 and no voltage is generated at its output, i.e. logical null is formed. The logical unit is formed at the output of the element of coincidence AND 62, which is a sign of recognition FMN-4 signal.

, то свертка его спектра осуществляется только на выходе умножителя фазы на восемь 49. При этом единичное напряжение появляется только на выходе элемента совпадения И 63.If the input with a panoramic receiver receives a signal with eight-fold phase shift keying FMN-8

, then the convolution of its spectrum is carried out only at the output of the phase multiplier by eight 49. In this case, a unit voltage appears only at the output of the AND 63 coincidence element.

Thus, the proposed device in comparison with the base object provides a determination of the multiplicity of phase manipulation of the received signal. Thus, the functionality of the device is expanded.

Claims (1)

A device for determining the frequency, type of modulation, and manipulation of received signals, comprising a receiving antenna, an input circuit, a high-frequency amplifier, a mixer, the second input of which is connected to the local oscillator output, an intermediate-frequency amplifier, a detector, a video amplifier, and vertically deflecting cathode ray tube plates the horizontally deflecting plates of which are connected to the output of the frequency sweep forming device, the control inputs of the input circuit, high-frequency amplifier, g the terody and frequency sweep forming devices are connected to the corresponding outputs of the search unit, which can be used as a sawtooth voltage generator or electric motor, connected in series to the output of the high-frequency amplifier, the first key, the second input of which is connected to the output of the detector, the first amplitude detector, the first high-pass filter, first quadrator, first voltage divider, the second input of which is connected through the first low-pass filter to the output of the first of the detector, and the first comparison unit, the two outputs of which are the first and second outputs of the device, a frequency detector, a second low-pass filter, a second quadrator and a second voltage divider, the second input of which is connected to the output of the first through a first spectrum analyzer key, and the output is connected to the second input of the first comparison unit, the second key is connected in series to the output of the first key, the second input of which is connected to the second output of the device, phase detector , a third low-pass filter, a second amplitude detector and a second comparison unit, the second input of which is connected through a second high-pass filter and a third amplitude detector connected to the output of the phase detector, and the two outputs are the third and fourth outputs of the device, connected in series to the output of the frequency detector a third high-pass filter, a fifth amplitude detector and a third comparison unit, the second input of which is connected through the fourth amplitude detector to the output of the second lower filter x frequencies, and two outputs are the fifth and sixth outputs of the device, a complex spectrum analyzer, a linear phase phase analyzer, a first analog-code converter and a first coincidence element And, the second input of which is through a series-connected amplitude symmetry analyzer, connected to the output of the first key and the second analog-to-code converter is connected to the second output of the complex spectrum analyzer, and the output is the seventh output of the device, connected in series to the outputs to the second analog-code converter, the first inverter and the second coincidence element AND, the second input of which is connected to the output of the first analog-code converter, and the output is the eighth output of the device, the second inverter and the third coincidence element And, connected to the output of the first analog-code converter, the second input of which is connected to the output of the first inverter, and the output is the ninth output of the device, characterized in that it is equipped with a code-voltage converter, a third key, a third and fourth inverter tori and three processing channels, each of which consists of a series-connected phase multiplier, a spectrum analyzer, a comparison unit, the second input of which is connected to the output of the first spectrum analyzer, an analog-to-code converter, and an AND element, and a code converter is connected in series to the ninth output of the device -voltage, the third switch, the second input of which is connected to the output of the first switch and three processing channels, the second input of the matching element And the first processing channel is connected to the output of the transform the analogue-code of the second processing channel, and the output is the tenth output of the device, the second input of the coincidence element And the second processing channel through the third inverter is connected to the converter output the analog-code of the first processing channel, and the output is the eleventh output of the device, the second input of the coincidence element And the third the processing channel is connected through the fourth inverter to the output of the analog-code converter of the second processing channel, and the output is the twelfth output of the device, in the first processing channel the phase is multiplied Xia twice in the second - four times in the third - eight times.

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