RU2321177C1 - Radio-technical surveillance station - Google Patents

Abstract

FIELD: radio engineering, possible use for conducting radio-technological surveillance of radio-electronic devices of possible opponent (radiolocation stations, communication and control radio lines, etc).

SUBSTANCE: claimed radio-technical surveillance station contains antenna device, receiver, direction-finding device, analyzer of parameters of received signal, device for memorizing and processing received information and telemetric device, manufactured and interconnected in a certain manner.

EFFECT: increased interference resistance and trustworthiness of signal receipt of radio-electronic devices by means of suppressing the false signals received through additional channels.

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Description

The proposed station belongs to the field of radio engineering and allows radio-technical reconnaissance of radio-electronic means (RES) of a potential enemy (radar, radio communication and control lines, etc.).

Known stations and reconnaissance systems for radiation from the potential enemy’s RES (RF patents No. 2136110, 2150178, 2275746; US patents No. 3806926, 3891989, 3896439; Germany patent No. 3346155; UK patent No. 1587357; France patent No. 2447041; S. Vakin, Shustov LN Fundamentals of Radio Countermeasures and Radio Engineering Intelligence (Moscow: Sov. Radio, 1968, p. 382, Fig. 10.2, etc.).

Of the known stations and systems closest to the proposed one is the "Radio intelligence station" (RF patent No. 2275746, Н04K 3/00, 2004), which is chosen as the base.

The specified station contains an antenna device 1, a receiver 2, a direction-finding device 3, an analyzer 4 of the parameters of the received signal, a device 5 for storing and processing the received information, a telemetry device 6, receiving antennas 7-9, a tuner 10, the first 11 and second 23 local oscillators, mixers 12-14 and 24, amplifiers 17-19 of the first intermediate frequency, detector 20, first 21 and second 31 delay lines, key 22, amplifier 25 of the second intermediate frequency, multiplier 26, 27 and 30, narrow-band filters 28, 29 and 32, phase detector 33, phase meters 34 and 35, an engine 15 and a reference generator 16.

The panoramic receiver station 2 ELINT the same value of the first intermediate frequency ω _pr1 may be obtained as a result of receiving signals under exploration at two frequencies ω _s and ω _s, i.e.

ω _pr1 = ω _s -ω _g1 and φ _pr1 = φ _g1 -φ _s .

Therefore, if the tuning frequency ω _to take over the main receiving channel, along with it will be a mirror receiving channel frequency ω _of which differs from the frequency ω _with 2ω _pr1 and located symmetrically (mirror) relative to frequency ω _z1 oscillator 11 (Figure .2). Conversion of image channel reception takes place with the same conversion coefficient K, _etc., as the main channel. Therefore, it most significantly affects the selectivity and noise immunity of the panoramic receiver.

In addition to the mirror, there are other additional (combinational) reception channels. In general terms, any Raman receive channel occurs when the condition

ω _pr1 = | ± m · ω _ki ± n · ω _g1 |,

where ω _ki is the frequency of the i-th Raman reception channel;

m, n, i are positive integers, including n = 0.

The most harmful combinational reception channels are those generated by the interaction of the first harmonic of the signal frequency with the harmonics of the frequency of the first local oscillator 11 of a small order (second, third, etc.), since the sensitivity of the panoramic receiver through these channels is close to the sensitivity of the main channel. So, two combinational channels with m = 1 and n = 2 correspond to frequencies:

ω _k1 = 2ω _{g1 -ω pr1} and φ _k2 = 2φ _g1 + φ _pr1 .

If the carrier frequency of the interference is equal to the first intermediate frequency, a forward channel is formed.

If the output of the panoramic receiver receives two powerful false signals (interference) at frequencies ω ₁ and ω ₂ or several powerful signals (interference) in the frequency band Δω ₁ "left" of the passband Δω _{n of the} panoramic receiver or two powerful false signals (interference) at frequencies ω ₃ and ω ₄ or several powerful signals (interference) in the frequency band Δω ₂ "to the right" of the passband Δω _{n of the} panoramic receiver, then intermodulation channels are formed.

The presence of false signals (interference) received through the direct channel, the mirror channel, Raman and intermodulation channels, leads to a decrease in noise immunity and the reliability of the reception of signals from reconnaissance electronic equipment.

An object of the invention is to increase the noise immunity and reliability of reception of signals of reconnaissance RES by suppressing false signals (interference) received via additional channels.

The problem is achieved in that the radio intelligence station, containing, in accordance with the closest analogue, a direction-finding device, an antenna device and series-connected receiver, an analyzer of parameters of the received signal, a device for storing and processing the received information and a telemetry device, the output of which is the output of the station, while the receiver made in the form of a receiving antenna, connected in series with the first mixer, the second input of which is connected through the first local oscillator to the tuner, and the first amplifier of the first intermediate frequency, connected in series with the detector, the second input of which through the first delay line is connected to its output, the first key, the second mixer, the second input of which is connected to the output of the second local oscillator, and the amplifier of the second intermediate frequency, the output of which is the receiver output, the control input of the tuning unit is connected to the detector output, the direction-finding device is made in the form of two direction-finding channels, each of which consists of a receiver antenna, mixer, the second input of which is connected to the output of the first local oscillator, an amplifier of the first intermediate frequency, a multiplier, the second input of which is connected to the output of the amplifier of the second intermediate frequency, and a narrow-band filter, the third multiplier, the second input, are connected in series to the output of the first narrow-band filter which is connected to the output of the second narrow-band filter, the third narrow-band filter and the first phase meter, to the output of the second narrow-band filter in series the second delay line is turned on, a phase detector, the second input of which is connected to the output of the second narrow-band filter, and the second phase meter, the second inputs of the phase meters are connected to the output of the reference generator, and the outputs are connected to a device for storing and processing the received information, the antenna device contains three receiving antennas, a receiving the receiver antenna is located above the rotor hub of the helicopter, the receiving antennas of the direction-finding device are located at the ends of the rotor blades of the helicopter, the engine is kinematically connected to the rotor m of the helicopter and the reference generator, differs from the closest analogue in that the receiver is equipped with a fourth and fifth narrow-band filters, three phase inverters, four adders, two bandpass filters, two 90 ° phase shifters, a fifth mixer, a fourth amplifier of the first intermediate frequency, a fourth multiplier, and a second a key and an amplitude detector, and a fourth narrow-band filter, a first phase inverter, a first adder, the second input of which is connected to the receiver receiving antenna, the first bandpass filter, the second phase inverter, the second adder, the second input of which is connected to the output of the first adder, the second bandpass filter, the third phase inverter and the third adder, the second input of which is connected to the output of the second adder, and the output is connected to the first input of the first mixer , the first phase shifter 90 °, the fifth mixer, the second input of which is connected to the output of the third adder, the fourth amplifier of the first intermediate hour are connected in series to the second output of the first local oscillator the second phase shifter 90 °, the fourth adder, the second input of which is connected to the output of the first amplifier of the first intermediate frequency, the fourth multiplier, the second input of which is connected to the output of the third adder, the fifth narrow-band filter, the amplitude detector and the second switch, the second input of which is connected to the output of the fourth adder, and the output is connected to the first input of the detector and to the second input of the first key.

The structural diagram of the proposed radio intelligence station is presented in figure 1. Frequency diagrams illustrating the formation of additional receiving channels are shown in FIG. The geometric arrangement of the receiving antennas on the helicopter is shown in Fig.3.

The radio intelligence station contains an antenna device 1, a receiver 2, a direction-finding device 3, an analyzer 4 of the received signal parameters, a device 5 for storing and processing the received information, and a telemetry device 6.

The receiver 2 contains a receiving antenna 7 connected in series, a fourth narrow-band filter 36, a first phase inverter 37, a first adder 38, the second input of which is connected to a receiving antenna 7, a first band-pass filter 39, a second phase inverter 40, and a second adder 41, the second input of which is connected to the output the first adder 38, the second bandpass filter 42, the third phase inverter 43, the third adder 44, the first mixer 12, the second input of which through the first local oscillator 11 is connected to the output of the tuning unit 10, and the first amplifier 17 of the first intermediate often you, serially connected to the second output of the first local oscillator 11, the first phase shifter 45 by 90 °, the fifth mixer 46, the second input of which is connected to the output of the adder 44, the fourth amplifier 47 of the first intermediate frequency, the second phase shifter 48 by 90 °, the fourth adder 49, the second input which is connected to the output of the amplifier 17 of the first intermediate frequency, the fourth multiplier 50, the second input of which is connected to the output of the adder 44, the fifth narrow-band filter 51, the amplitude detector 52, the second key 53, the second input of which is connected to the output m of the adder 49, the detector 20, the second input of which through the first delay line 21 is connected to its output, the first key 22, the second input of which is connected to the output of the key 53, the second mixer 24, the second input of which is connected to the output of the second local oscillator 23, and amplifier 25 the second intermediate frequency, the output of which is the output of the receiver 2 and is connected to the input of the analyzer 4 parameters of the received signal.

The direction-finding device 3 contains two direction-finding channels, each of which contains a receiving antenna 8 (9) in series, a mixer 13 (14), the second input of which is connected to the output of the local oscillator 11, an amplifier 18 (19) of the first intermediate frequency, a multiplier 26 (27) , the second input of which is connected to the output of the amplifier 25 of the second intermediate frequency, a narrow-band filter 28 (29). At the same time, the third multiplier 30, the second input of which is connected to the output of the second narrow-band filter 29, the third narrow-band filter 32 and the first phase meter 34, are connected to the output of the first narrow-band filter 28, the second delay line 31, the phase detector 33 are sequentially connected to the output of the second narrow-band filter , the second input of which is connected to the output of the narrow-band filter 29, and the second phase meter 35. The second inputs of the phase meters 34 and 35 are connected to the output of the reference generator 16, and the outputs are connected to the storage device 5 processing the information received. The antenna device 1 contains three receiving antennas 7-9, the receiving antenna 7 of the receiver 2 is located above the rotor hub of the helicopter, the receiving antennas 8 and 9 of the direction-finding device 3 are located at the ends of the rotor blades of the helicopter (Fig. 3). The engine 15 is kinetically connected with the helicopter propeller and the reference generator 16.

The radio intelligence station operates as follows.

The station is located on board a helicopter. The presence of a rotary rotor of the helicopter is used to determine the direction to the radiating RES using an antenna device 1, receiving antennas 8 and 9 of which are located at the ends of the rotor blades (Fig. 3).

Signals received by antennas 7-9, for example with phase shift keying (PSK)

U ₁ (t) = υ ₁ · Cos [(ω _c ± Δω) t + φ _k (t) + φ _s ],

U ₂ (t) = υ ₂ · Cos [(ω _c ± Δω) t + φ _k (t) + 2π · R / λCos (Ω-α)],

U ₃ (t) = υ ₃ · Cos [(ω _c ± Δω) t + φ _k (t) -2π · R / λCos (Ω-α)], 0≤t≤T _c ,

where υ ₁ , υ ₂ , υ ₃ are the amplitudes of the RES signal;

ω _s is the carrier frequency of the RES signal;

φ _with - the initial phase of the signal RES;

T _with - the duration of the signal RES;

± Δω - instability of the carrier frequency of the signal due to various destabilizing factors;

φ _k (t) = {0, π} is the manipulated component of the phase, which displays the law of phase manipulation in accordance with the modulating code;

R is the radius of the circle on which the receiving antennas 8 and 9 are located;

 Ω = 2π · R is the rotation speed of the receiving antennas 8 and 9 around the receiving antenna 7 (rotational speed of the helicopter rotor);

α - bearing (azimuth) to the radiating RES,

arrive at the first inputs of the mixers 13, 14 and through the adders 38, 41 and 44, which have only one shoulder, to the first inputs of the mixers 12 and 46. The voltage of the first local oscillator 11 of a ramp frequency is applied to the second inputs of these mixers:

U _g1 (t) = υ _g1 · Cos (ω _g1 t + πγt ² + φ _g1 ),

U _g1 '(t) = υ _g1 · Cos (ω _g1 t + πγt ² + φ _g1 + 90 °), 0≤t≤T _p ,

where γ = Df / T _p is the rate of change of the local oscillator frequency.

It should be noted that the search for the PSK signals of the potential enemy’s RES in a given frequency range Df is performed using the tuning unit 10, which periodically with a period T _p changes the frequency ω _{g1 of the} local oscillator 11 according to a sawtooth law.

At the output of the mixers 12, 46, 13 and 14, voltages of combination frequencies are generated. Amplifiers 17, 47, 18 and 19 distinguish the voltage of the first intermediate frequency, respectively:

U _CR1 (t) = υ _CR1 · Cos [(ω _CR1 ± Δω) t + φ _k (t) -πγt ² + φ _CR1 ],

U _CR2 (t) = υ _CR1 · Cos [(ω _CR1 ± Δω) t + φ _k (t) -πγt ² + φ _CR1 -90 °],

U _pr3 (t) = υ _pr2 · Cos [(ω _pr1 ± Δω) t + φ _k (t) -πγt ² + 2π · R / λCos (Ω-α)],

U _CR4 (t) = υ _CR3 · Cos [(ω _CR1 ± Δω) t + φ _k (t) -πγt ² -2π · R / λCos (Ω-α)], 0≤t≤T _c ,

where υ _pr1 = 1 / 2k ₁ · υ ₁ · υ _g1 ;

υ _pr2 = 1 / 2k ₁ · υ ₂ · υ _g1 ;

υ _pr3 = 1 / 2k ₁ · υ ₃ · υ _g1 ;

k ₁ - gear ratio of the mixers;

ω _CR1 = ω _with -ω _g1 - the first intermediate frequency;

φ _pr1 = φ _s -φ _g1 .

The voltage U _pr2 (t) from the output of the amplifier 47 of the first intermediate frequency is supplied to the input of the phase shifter 48 by 90 °, at the output of which a voltage is generated

U _CR4 (t) = υ _CR1 · Cos [(ω _CR1 ± Δω) t + φ _k (t) -πγt ² + φ _CR1 -90 ° + 90 °] =

= υ _pr1 · Cos [(ω _pr1 ± Δω) t + φ _k (t) -πγt ² + φ _pr1 ].

Voltages U _CR1 (t) and U _CR4 (t) are supplied to two inputs of the adder 49, at the output of which the total voltage is formed

U _Σ (t) = υ _Σ · Cos [(ω _CR1 ± Δω) t + φ _k (t) -πγt ² + φ _CR1 ], 0≤t≤T _c ,

where υ _Σ = 2υ _pr1 .

This voltage is supplied to the second input of the multiplier 50, the first input of which receives the received signal U ₁ (t) from the output of the adder 44. A voltage is generated at the output of the multiplier 50

U _g (t) = υ _g Cos (ω _g1 t + πγt ² + φ _g1 ), 0≤t≤T _p ,

where υ _g = 1 / 2k ₂ · υ ₁ · υ _Σ ;

k ₂ - transfer coefficient of the multiplier.

The tuning frequency ω _{n1 of the} narrow-band filter 36 is chosen equal to the first intermediate frequency ω _pr1

ω _n1 = ω _pr1 .

The tuning frequency ω _{n2 of the} narrow-band filter 51 is chosen equal to the initial frequency of the first local oscillator ω _g1

ω _n2 = ω _g1 .

The tuning frequency ω _n3 and the passband Δω _{p1 of the} band-pass filter 39 is selected as follows:

ω _n3 = (ω ₁ + ω ₂ ) / 2, Δω _n1 = ω ₂ -ω ₁ ,

where ω ₁ , ω ₂ are the frequencies of two possible powerful signals, the appearance of which in the frequency band Δω ₁ located "to the left" of the passband Δω _{p of the} receiver leads to the formation of intermodulation interference.

The tuning frequency ω _n4 and the passband Δω _{p2 of the} bandpass filter 42 are selected as follows:

ω _n4 = (ω ₃ + ω ₄ ) / 2, Δω _n2 = ω ₄ -ω ₃ ,

where ω ₃ , ω ₄ are the frequencies of two possible powerful signals, the appearance of which in the frequency band Δω ₂ located "to the right" of the passband Δω _{p of the} receiver leads to the formation of intermodulation interference.

Voltage U _d (t) is allocated a narrow-band filter 51 is detected by an amplitude detector 52 and applied to the control input of the switch 53, opening it. Keys 22 and 53 in the initial state are always closed.

In this case, the voltage U _Σ (t) from the output of the adder 49 through the public key 53 is supplied to the input of the detector 20. When a RES signal is detected, a constant voltage appears at the output of the detector 20, which is supplied to the control input of the tuning unit 10, turning it off, to the control input of the key 22, opening it, and to the input of the delay line 21. The delay time τ _{s of} the delay line 21 is selected so that it is possible to fix the detected PSK signal and analyze its parameters.

When you turn off the tuning unit 10 amplifiers 17, 47, 18 and 19 the following voltages are allocated:

U _CR5 (t) = υ _CR1 · Cos [(ω _CR1 ± Δω) t + φ _k (t) + φ _CR1 ],

U _CR6 (t) = υ _CR1 · Cos [(ω _CR1 ± Δω) t + φ _k (t) + φ _CR1 -90 °],

U _CR7 (t) = υ _CR2 · Cos [(ω _CR1 ± Δω) t + φ _k (t) + 2π · R / λ · Cos (Ω-α)],

U _pr8 (t) = υ _pr3 · Cos [(ω _pr1 ± Δω) t + φ _k (t) -2π · R / λ · Cos (Ω-α)], 0≤t≤T _c ,

At the output of the adder 49 in this case, the following total voltage

U _Σ1 (t) = υ _Σ · Cos [(ω _CR1 ± Δω) t + φ _k (t) + φ _CR1 ], 0≤t≤T _s ,

which through the public key 22 enters the first input of the mixer 24, the second input of which is supplied with the voltage of the second local oscillator 23 with a stable frequency ω _g2

U _g2 (t) = υ _g2 · Cos (ω _g2 t + φ _g2 ).

At the output of the mixer 24, voltages of combination frequencies are generated. The amplifier 25 is allocated the voltage of the second intermediate frequency

U _pr9 (t) = υ _pr9 · Cos [(ω _pr2 ± Δω) t + φ _k (t) + φ _pr9 ], 0≤t≤T _s ,

where υ _pr9 = 1 / 2k ₁ · υ _Σ1 · υ _g2 ;

_np2 ω = ω _z2 -ω _pr1 - second intermediate frequency;

cp = φ _{pr9 pr1} -φ _r2,

which is fed to the input of the analyzer 4 of the received signal, where the duration τ _{E of the} elementary packages from which the QPSK signal is composed, their number N (T _C = N · τ _E ) and the law of phase manipulation are determined.

The voltage U _pr9 (t) from the output of the amplifier 25 of the second intermediate frequency is simultaneously supplied to the second inputs of the multipliers 26 and 27 direction finding channels, the first inputs of which receive the voltage U _pr7 (t) and U _pr8 (t) from the outputs of the amplifiers 18 and 19 of the first intermediate frequencies respectively. At the outputs of multipliers 26 and 27, phase-modulated (FM) voltages are formed at a stable frequency ω _{g2 of the} second local oscillator:

U ₄ (t) = υ ₄ · Cos [(ω _g2 t + φ _g2 + 2π · R / λ · Cos (Ω-α)],

₅ U (t) = υ ₅ · Cos [((ω t + φ _{r2 r2} -2π · R / λ · Cos ( Ω-α)], 0≤t≤T _c,

where υ ₄ = 1 / 2k ₂ · υ _pr2 · υ _pr9 ;

υ ₅ = 1 / 2k ₂ · υ _pr3 · ^· υ _pr9 ;

which are distinguished by narrow-band filters 28 and 29 with a tuning frequency of ω _n = ω _g2 .

The signs “+” and “-” before the value 2π · R / λ · Cos (Ω-α) correspond to diametrically opposite locations of the antennas 8 and 9 at the ends of the rotor blades of the helicopter relative to the receiving antenna 7 located above the helicopter rotor hub.

Therefore, useful information about the bearing α is transferred to the stable frequency ω _{g2 of the} second local oscillator 23. Therefore, the instability ± ω of the carrier frequency caused by various destabilizing factors and the type of modulation (manipulation) of the received RES signal do not affect the direction finding result, thereby increasing the accuracy of positioning RES.

Moreover, the value that is part of these oscillations Δφ _m = 2π · R / λ, and called the phase modulation index, characterizes the maximum value of the phase deviation of the signals received by the rotating antennas 8 and 9, relative to the phase of the signal received by the fixed antenna 7.

The direction-finding device 3 is the more sensitive to a change in the angle α, the larger the relative size of the measuring phase R / λ. However, with increasing R / λ, the value of the angular coordinate α decreases, at which the phase difference exceeds 2π, i.e. ambiguity of reading the angle α occurs.

Therefore, for R / λ> 1/2, the counting α becomes ambiguous. The elimination of this ambiguity by reducing the R / λ ratio usually does not justify itself, since the main advantage of a wide-base system is lost. In addition, in the range of meter and especially decimeter waves, it is often not possible to take small values of R / λ due to design considerations.

In order to increase the accuracy of direction finding of RES in the horizontal (azimuthal) plane, receiving antennas 8 and 9 are located at the ends of the rotor blades of the helicopter. The displacement of signals from two diametrically opposite receiving antennas 8 and 9, located at the same distance R from the rotor axis of the rotor, causes phase modulation, obtained using one receiving antenna rotating in a circle whose radius R is two times larger (R ₁ = 2R )

Indeed, the output of the multiplier 30 produces a harmonic voltage

U ₆ (t) = υ ₆ Cos (Ω-α), 0≤t≤T _c ,

where υ ₆ = 1 / 2K ₂ · υ ₄ · υ ₅ ,

with phase modulation index

Δφ _m1 = 2π · R ₁ / λ,

where R ₁ = 2R,

which is allocated by a narrow-band filter 32 and fed to the first input of the phasemeter 34, the second input of which is supplied with the voltage of the reference oscillator 16

U ₀ (t) = υ ₀ Cos Cost.

The phasometer 34 provides an accurate but ambiguous measurement of the angular coordinate α. To eliminate the ambiguity in reading the angle α, it is necessary to reduce the phase modulation index without decreasing the R / λ ratio. This is achieved by using an autocorrelator consisting of a delay line 31 and a phase detector 33, which is equivalent to reducing the phase modulation index to

Δφ _m2 = 2π · d ₁ / λ,

where d ₁ <R.

A voltage is generated at the output of the autocorrelator

U ₇ (t) = υ ₆ Cos (Ω-α), 0≤t≤T _c ,

with the phase modulation index Δφ _m2 , which is supplied to the first input of the phasemeter 35, the voltage U ₀ (t) of the reference generator 16 is supplied to the second input. The phase meter 35 provides a rough but unambiguous measurement of the angle α.

The minimum distance R ₀ from the RES to the helicopter propeller is determined from the expression

F _q (t) ≈ (V ² · t ² ) / (λ · R ₀ ),

where F _q (t) is the Doppler frequency shift;

V = Ω · R;

λ is the wavelength.

The Doppler frequency shift is measured in the analyzer 4 parameters of the received signal, which also determines R ₀ . The latter are recorded in the device 5 for storing and processing the received information.

The location of the RES is determined in the device 5 by the measured values of α and R ₀ .

Telemetry device 6 is designed to transmit intelligence information to the control point.

After the time τ _{s, the} constant voltage from the output of the delay line 21 is supplied to the control input of the detector 20 and resets its contents to zero. In this case, the key 22 is closed, and the tuning unit 10 is turned on, i.e. they are translated into their original positions.

When a signal of the next enemy RES is detected, the operation of the radio intelligence station occurs in a similar way.

The operation of the radio intelligence station described above corresponds to the case of receiving useful QPSK signals on the main channel at a frequency of ω _s .

If a false signal (interference) is received on the mirror channel at a frequency of ω _s (figure 2)

U ₃ (t) = υ _З · Cos (ω _З t + φ _З ), 0≤t≤T _З ,

the amplifiers 17 and 47 distinguish the following voltages:

U _pr10 (t) = υ _pr10 · Cos (ω _pr1 t + πγt ² + φ _pr10 ),

U _pr11 (t) = υ _pr10 · Cos (ω _pr1 t + πγt ² + φ _pr10 + 90 °), 0≤t≤T _З ,

where υ _pr10 = 1 / 2k ₁ · υ _З · υ _g1 ;

ω _CR1 = ω _g1 -ω _Z - the first intermediate frequency;

ω _pr10 = ω _g1 -ω ₃ .

The voltage U _pr11 (t) from the output of the amplifier 47 of the first intermediate frequency is supplied to the input of the phase shifter 48 by 90 °, at the output of which a voltage is generated

U _pr12 (t) = υ _pr10 · Cos (ω _pr1 t + πγt ² + φ _pr10 + 90 ° + 90 °) =

= -υ _pr10 · Cos (ω _pr1 t + πγt ² + φ _pr10 ), 0≤t≤T _З ,

Voltages U _pr10 (t) and U _pr12 (t), supplied to the two inputs of the adder 49, are compensated at its output.

Therefore, a false signal (interference) received on the mirror channel at a frequency of ω ₃ is suppressed. For this, an “outer ring” is used, consisting of mixers 12 and 46, a local oscillator 11, amplifiers 17 and 47 of the first intermediate frequency, phase shifters 45 and 48 by 90 °, an adder 49 and implementing a phase compensation method.

For a similar reason, a false signal (interference) received on the first combination channel at a frequency ω _{k1 is also} suppressed.

If a false signal (interference) is received on the second Raman channel at a frequency ω _k2

U _k2 (t) = υ _k2 · Cos (ω _k2 t + φ _k2 ), 0≤t≤T _k2 ,

the amplifiers 17 and 47 distinguish the following voltages:

U _pr13 (t) = υ _pr13 · Cos (ω _pr1 t-πγt ² + φ _pr13 ),

U _pr14 (t) = υ _pr13 · Cos (ω _pr1 t-πγt ² + φ _pr13 -90 °), 0≤t≤T _k2 ,

where υ _pr13 = 1 / 2k ₁ · υk ₂ · υ _g1 ;

ω _pr1 = ω _k2 -2ω _g1 - the first intermediate frequency;

φ _pr13 = φ _k2 -φ _g1 .

The voltage U _pr14 (t) from the output of the intermediate frequency amplifier 47 is supplied to the input of the phase shifter 48 by 90 °, at the output of which a voltage is generated

U _pr15 (t) = υ _pr13 · Cos (ω _pr1 t-πγt ² + φ _pr13 -90 ° + 90 °) =

= υ _pr13 · Cos (ω _pr1 t-πγt ² + φ _pr13 ), 0≤t≤T _k2 .

Voltages U _pr13 (t) and U _pr15 (t) are supplied to two inputs of the adder 49, at the output of which the total voltage is formed

U _Σ2 (t) = υ _Σ2 Cos (ω _pr1 t-πγt ² + φ _pr13 ),

where υ _Σ2 = 2υ _pr13 .

This voltage is supplied to the second input of the multiplier 50, the first input of which receives the received false signal (interference) U _k2 (t). At the output of the multiplier 50, a voltage is generated

U ₈ (t) = υ ₈ Cos (2ω _g1 t + πγt ² + φ _g1 ), 0≤t≤T _k2 ,

where υ ₈ = 1 / 2k ₂ · υ _k2 · υ _Σ2 ;

which does not fall into the passband of the narrow-band filter 51. The key 53 does not open and the false signal (interference) received on the second combination channel at a frequency ω _k2 is suppressed. For this, an “inner ring” is used, consisting of a multiplier 50, a narrow-band filter 51, an amplitude detector 52, a key 53, and implementing the narrow-band filtering method.

If a false signal (interference) is received through the direct channel at a frequency ω _pr1

U _n1 (t) = υ _n1 · Cos (ω t + φ _{pr1 n1),} 0≤t≤T _n1

then it comes from the output of the receiving antenna 7 to the first input of the adder 38, is allocated by a narrow-band filter 36 tuned to the first intermediate frequency ω _pr1 , phase inverted by 180 ° in the phase inverter 37

_N1 U '(t) = - υ _n1 · Cos (ω t + φ _{pr1 n1),} 0≤t≤T _n1.

The _voltages U _p1 (t) and U _p1 '(t) supplied to the two inputs of the adder 38 are compensated at its output.

Therefore, a false signal (interference) received through the direct passage channel at the first intermediate frequency ω _pr1 is suppressed by a filter plug consisting of a narrow-band filter 36, a phase inverter 37, an adder 38, and implementing a phase compensation method.

If two powerful false signals (interference) at frequencies ω ₁ and ω ₂ or several powerful signals (interference) appear simultaneously in the frequency band Δω ₁ "to the left" of the passband Δω _{n of the} receiver, capable of generating intermodulation interference, then they are separated by a band-pass filter 39 are phase inverted by 180 ° by the phase inverter 40 and compensated in the adder 41.

Consequently, false signals (interference) received in the frequency band Δω ₁ and generating intermodulation interference are suppressed by a filter plug consisting of a bandpass filter 39, a phase inverter 40, an adder 41 and implementing a phase compensation method.

If two powerful false signals (interference) at frequencies ω ₃ and ω ₄ or several powerful signals (interference) appear simultaneously in the frequency band Δω ₂ "to the right" of the passband Δω _{p of the} receiver, capable of generating intermodulation interference, then they are separated by a band-pass filter 42 are phase inverted by 180 ° by the phase inverter 43 and compensated in the adder 44.

Consequently, false signals (interference) received in the frequency band Δω ₂ and generating intermodulation interference are suppressed by the filter plug, consisting of a bandpass filter 42, a phase inverter 43, an adder 44 and implements a phase compensation method.

The helicopter flight path, on board of which a radio intelligence station is located, is usually laid in the border areas without violating the airspace of the likely enemy and without diplomatic complications.

The radio intelligence station provides accurate and unambiguous determination of the location of the radio electronic equipment. In this case, the direction-finding device is invariant to the type of modulation (manipulation) and instability of the carrier frequency of the reconnoitered signals.

Thus, the proposed radio intelligence station, in comparison with the prototype and other technical solutions of a similar purpose, provides increased noise immunity and the reliability of the reception of signals from reconnaissance RES. This is achieved by suppressing false signals (interference) received via additional channels (direct channel, mirror, Raman and intermodulation channels).

Claims (1)

A radio intelligence station containing a direction-finding device, an antenna device and a receiver in series, an analyzer of the parameters of the received signal, a device for storing and processing the received information and a telemetry device, the output of which is the output of the station, the receiver is made in the form of a receiving antenna, connected in series with the first mixer, the second input of which through the first local oscillator is connected to the output of the tuning unit, and the first amplifier of the first intermediate frequency, p therefore included a detector, the second input of which through the first delay line is connected to its output, the first key, the second mixer, the second input of which is connected to the output of the second local oscillator, and the amplifier of the second intermediate frequency, the output of which is the output of the receiver, the control input of the tuning unit is connected to the output detector, direction-finding device is made in the form of two direction-finding channels, each of which consists of a series-connected receiving antenna, a mixer, the second input of which dinene with the output of the first local oscillator, the amplifier of the first intermediate frequency, the multiplier, the second input of which is connected to the output of the amplifier of the second intermediate frequency, and a narrow-band filter, the third multiplier is connected in series to the output of the first narrow-band filter, the second input of which is connected to the output of the second narrow-band filter, the third narrow-band filter and the first phase meter, the second delay line, a phase detector, the second input of which is connected to the output of the second narrow-band filter n with the output of the second narrow-band filter, and the second phase meter, the second inputs of the phase meters are connected to the output of the reference generator, and the outputs are connected to a device for storing and processing the received information, the antenna device contains three receiving antennas, the receiving antenna of the receiver is located above the helicopter rotor hub, receiving antennas of direction finding the devices are located at the ends of the rotor blades of the helicopter, the engine is kinematically connected with the helicopter rotor and the reference generator, characterized in that the receiver is equipped with an even the fourth and fifth narrow-band filters, three phase inverters, four adders, two band-pass filters, two 90 ° phase shifters, the fifth mixer, the fourth amplifier of the first intermediate frequency, the fourth multiplier, the second key and the amplitude detector, and the fourth narrow-band filter is connected in series to the receiving antenna of the receiver , the first phase inverter, the first adder, the second input of which is connected to the receiving antenna of the receiver, the first bandpass filter, the second phase inverter, the second adder, sec the first input of which is connected to the output of the first adder, the second bandpass filter, the third phase inverter and the third adder, the second input of which is connected to the output of the second adder, and the output is connected to the first input of the first mixer, the first phase shifter 90 ° is connected in series to the second output of the first local oscillator, the fifth mixer, the second input of which is connected to the output of the third adder, the fourth amplifier of the first intermediate frequency, the second phase shifter 90 °, the fourth adder, the second input of which is connected to the output of the first of the amplifier of the first intermediate frequency, the fourth multiplier, the second input of which is connected to the output of the third adder, the fifth narrow-band filter, the amplitude detector and the second key, the second input of which is connected to the output of the fourth adder, and the output is connected to the first input of the detector and to the second input of the first key .

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