RU2308156C2 - System for transmitting quaternary-encoded radio signals - Google Patents

Abstract

FIELD: communications engineering, possible use in synchronous and asynchronous communication lines.

SUBSTANCE: the system for transmitting quaternary-encoded radio signals contains transmitting section, to which through distribution route the input of receiving part is connected, where transmitting part contains clock impulse generator, generator of D-codes, generator of pseudo-random numbers, frequencies synthesizer, modulator, generator of signals of double frequency manipulation and block for controlling frequency shift, and receiving part contains demodulator, clock impulse generator, frequency synthesizer, pseudo-random numbers generator, block for selecting additional series, two-channel matched filter, subtracter, adjustable signal selector, block for controlling frequency shift and solving block.

EFFECT: increased interference resistance and trustworthiness under effect of intentional imitating interference.

4 cl, 7 dwg

Description

The invention relates to communication technology and can be used in synchronous and asynchronous communication systems for transmitting discrete information and synchronization using the propagation of electromagnetic waves in communication channels with pseudo-random tuning of the operating frequency (PFC) and unstable signal parameters (phase, amplitude and polarization) meter and decameter wavelengths when exposed to deliberate simulating interference (coinciding with the structure of the useful signal).

The known system for transmitting quaternary-coded radio signals according to the patent of the Russian Federation No. 2188516, IPC ⁷ H04L 27/26, decl. 05.21.01, publ. 08/27/02, Bull. No. 24, consists of a transmitting part, which contains a clock pulse generator, a D-code generator, a double frequency-shift signal driver, connected via a propagation path to a receiving part, which contains a signal selector, an additional sequence extraction unit, a two-channel matched filter, a subtractor, and a decider block similar to the proposed system. Moreover, in the known system, double frequency shift keying is used to transmit quadruply-encoded sequences.

The disadvantages of such a system for transmitting quadruple-coded radio signals are the low noise immunity under the influence of intentional imitating interference (coinciding with the structure of the useful signal) and the relatively low reliability in the radio channels with random signal parameters (phase, amplitude and polarization) of the meter and decameter wavelengths, which limits the region application of this system.

A well-known quadruple-coded radio transmission system described in Roland Wilson and John Richter's article "Generation and Performance of Quadraphase Welti Codes for Radar and Synchronization of Coherent and Differentially Coherent PSK" (IEEE Transactions on Communications, vol. COM-27, NO. 9 , September 1979, p.1296-1301) consists of a transmitting side, which contains a clock, a D-code generator, a phase modulator, a radio frequency generator, a switch and a phase shifter connected through a communication channel to a receiving side, which contains phase demodulators, filters low pass, matching Velty filter, subt Tutelo, decider similar proposed system. Moreover, in the known system, relative phase shift keying is used to transmit the quaternary-encoded sequences.

The disadvantages of such a system for transmitting quadruple-coded radio signals are the low noise immunity under the influence of intentional imitating interference (coinciding with the structure of the useful signal) and the relatively low reliability in the radio channels with random signal parameters (phase, amplitude and polarization) of the meter and decameter wavelengths, which limits the region application of this system.

The closest in technical essence and the functions performed to the claimed system for transmitting quaternary-coded radio signals, an analogue (prototype), is a system for transmitting quaternary-coded radio signals, see RF patent No. 2208915, IPC ⁷ H04L 3/00, declared. 11.24.02, publ. 07.20.03, Bull. No. 20. The known system, like the proposed transmission system, contains a transmitting part consisting of a clock pulse generator, a D-code generator, a modulator, a frequency synthesizer, a pseudo-random number generator, a propagation path, a receiving part consisting of a demodulator, a frequency synthesizer, a pseudo-random number generator, a clock pulse generator, an additional sequence allocation unit, a two-channel matched filter, a subtractor and a decision unit, similar to the proposed system. In addition, the transmitting part of the system contains a signal driver of double frequency manipulation, and the receiving part of the system contains a signal selector.

At the same time, in the known system for transmitting Quaternary-coded radio signals, as well as the proposed system for transmitting Quaternary-coded radio signals, in the transmitting part, the output of the clock generator is connected to the input of the generator of D-codes, a frequency synthesizer and a pseudo-random number generator. In this case, the n-control outputs of the pseudo-random number generator, where n≥2 is an integer, are connected to the corresponding n-control inputs of the frequency synthesizer, the output of which is connected to the modulating input of the modulator. The output of the modulator is the output of the transmitting part of the system and is connected through the propagation path to the input of the receiving part of the system. The receiving part of the system includes a demodulator, the information input of which is the input of the receiving part of the system, a clock generator, the output of which is connected to the clock inputs of the frequency synthesizer and pseudo random number generator, the n-control outputs of which are connected to the corresponding n-control inputs of the frequency synthesizer. The output of the frequency synthesizer is connected to the modulating input of the demodulator. The first and second information outputs of the additional sequences extraction unit are connected respectively to the first and second information inputs of a two-channel matched filter, the first and second information outputs of which are connected respectively to the first and second information inputs of the subtractor, the deciding block whose output is the output of the receiving part of the system. In addition, in the transmitting part of the system, the output of the clock generator is also connected to the clock input of the signal generator of the double frequency manipulation. The output of the generator of D-codes is connected to the information input of the signal generator of double frequency manipulation, the output of which is connected to the information input of the modulator. In the receiving part of the system, the demodulator output is connected to a signal selector, the first, second, third, and fourth information outputs of which are connected to the first, second, third, and fourth information inputs of the additional sequence allocation unit, respectively.

The transmission system of quaternary-coded radio signals - prototype uses to transmit the quaternary-coded sequence of two-fold frequency shift keying with frequency hopping, where odd elements quaternary-coded sequence is transmitted at frequencies f ₃ + f _{Frequency Hopping} or f ₄ + f _{Frequency Hopping,} and even elements quaternary-coded sequence are transmitted at frequencies f ₁ + f ₂ f _{frequency hopping} or _{frequency hopping} + f, i.e. nominal frequency determines the number of additional sequence in the quaternary-coded signal.

The disadvantage of this quadruple-coded radio signal transmission system is its low noise immunity when deliberate simulating interference (coinciding with the structure of the useful signal) in the radio channels with random signal parameters (phase, amplitude and polarization) of the meter and decameter wavelength ranges with frequency hopping, which limits the scope of this system. This is due to the fact that the frequency shift between the frequency channels of the quaternary-encoded radio signal remains constant during operation of the system in the frequency hopping mode, which increases the probability of suppressing the useful signal by intentional imitating interference (coinciding with the structure of the useful signal), which increases the likelihood of erroneous reception of the minimized four-fold coded sequence.

The objective of the invention is to develop a system for transmitting Quaternary-encoded radio signals, ensuring the achievement of a technical result, which consists in expanding the scope due to nonlinear pseudo-random changes in the frequency shift between the private channels of the Quaternary-encoded radio signal when the system is in the frequency hopping mode, increasing noise immunity and reliability in communication channels random signal parameters (phase, amplitude and polarization) of the meter and decameter wave ranges without p extending the frequency resource and reducing the system capacity, and is intended for synchronous and asynchronous communication systems in the transmission of discrete information and synchronization.

The quad-coded radio signal transmission system contains in the transmitting part a clock pulse generator, the output of which is connected to the input of the D-code generator, to the clock inputs of the frequency synthesizer and pseudorandom number generator. In this case, the n-control outputs of the pseudo-random number generator, where n≥2 is an integer, are connected to the corresponding n-control inputs of the frequency synthesizer, the output of which is connected to the modulating input of the modulator. The output of the modulator is the output of the transmitting part of the system and is connected through the propagation path to the input of the receiving part of the system. The receiving part of the system includes a demodulator, the information input of which is the input of the receiving part of the system, a clock generator, the output of which is connected to the clock inputs of the frequency synthesizer and pseudo random number generator. In this case, the n-control outputs of the pseudo-random number generator are connected to the corresponding n-control inputs of the frequency synthesizer, the output of which is connected to the modulating input of the demodulator. The first and second information outputs of the additional sequences extraction unit are connected respectively to the first and second information inputs of a two-channel matched filter, the first and second information outputs of which are connected respectively to the first and second information inputs of the subtractor. The output of the subtractor is connected to a decision block, the output of which is the output of the receiving part of the system.

The technical result in the implementation of the invention is to increase the noise immunity and reliability under the influence of intentional imitating interference (coinciding with the structure of the useful signal) is achieved by introducing a frequency shift control unit and a signal shaper of double frequency manipulation with a variable frequency shift into the transmitting part of the system, and the control unit system into the receiving part frequency shift and tunable signal selector. At the same time, in the transmitting part of the transmission system, the output of the clock generator is also connected to the clock inputs of the signal generator of double frequency manipulation with a variable frequency shift and to the frequency shift control unit. The output of the frequency synthesizer is also connected to the information input of the frequency shift control unit, the output of which is connected to the control input of the signal generator of double frequency manipulation with a variable frequency shift. The output of the generator of D-codes is connected to the information input of the signal generator of double frequency manipulation with a variable frequency shift, the output of which is connected to the information input of the modulator. Moreover, in the receiving part of the transmission system, the output of the clock generator is also connected to the clock input of the frequency shift control unit. The output of the frequency synthesizer is also connected to the information input of the frequency shift control unit, the output of which is connected to the control input of the tunable signal selector. The output of the demodulator is connected to the information input of a tunable signal selector, the first, second, third and fourth information outputs of which are the first, second, third and fourth information inputs of the additional sequences extraction unit.

In the particular case of execution, the signal driver of double frequency manipulation with a variable frequency shift can consist of the first and second varicap arrays, the first and second diodes, as well as a parallel oscillatory circuit consisting of a capacitor and inductance. In this case, the anodes of the first sections of the first and second varicap matrix, as well as the first tap of the parallel oscillatory circuit are jointly connected and are the output of the shaper of double frequency manipulation with a variable frequency shift. The anode of the second section of the first varicap array is connected to the cathode of the first diode and is a clock input of the shaper of double frequency manipulation with a variable frequency shift. The anode of the second section of the second varicap array is connected to the cathode of the second diode and is the information input of the shaper of double frequency manipulation with a variable frequency shift. The control inputs of the first and second varicap matrix are jointly connected and are the control input of the shaper of double frequency manipulation with a variable frequency shift. The anodes of the first and second diodes, as well as the second tap of the parallel oscillatory circuit are jointly connected to a common ground bus.

The frequency shift control unit may consist, for example, of a low-pass filter, a frequency detector and a frequency divider with a division factor of four. The input of the frequency divider with a division factor of four is the information input of the frequency shift control unit. The output of the frequency divider with a division factor of four is connected to the information input of the frequency detector, the clock input of which is the clock input of the frequency shift control unit. The output of the frequency detector is connected to the input of the low-pass filter, the output of which is the output of the frequency shift control unit.

The tunable signal selector may consist, for example, of the first, second, third and fourth tunable bandpass filters. The information inputs of the first, second, third and fourth tunable band-pass filters are combined and are the information input of the tunable signal selector. In this case, the controlled inputs of the first, second, third and fourth tunable bandpass filters are also combined and are the control input of the tunable signal selector. The outputs of the first, second, third and fourth tunable bandpass filters are respectively the first, second, third and fourth information outputs of the tunable signal selector.

Due to the introduction of a frequency-shift control unit to the transmitting part of the system, a double-frequency manipulation signal generator with a variable frequency shift, and to the receiving part of the frequency shift control unit and a tunable signal selector, a nonlinear pseudorandom change of the frequency shift between the frequency channels of the quad-coded radio signal is realized during operation system in the frequency hopping mode, which reduces the likelihood of suppressing the useful signal intentionally simulating hoi (coinciding with the useful signal structure), thereby decreasing the likelihood of erroneous reception folded quaternary-coded sequence.

The analysis of the prior art by the applicant, including a search by patent and scientific and technical sources of information, and the identification of sources containing information about analogues of the claimed invention, allowed to establish that the applicant did not find an analogue characterized by features identical to all essential features of the claimed invention. The selection from the list of identified analogues of the prototype, as the closest in the set of essential features of the analogue, allowed to identify the set of essential distinguishing features in relation to the applicant's technical result in the claimed device set forth in the claims. Therefore, the claimed invention meets the criterion of "novelty."

To verify compliance of the claimed invention with the criterion of "inventive step", the applicant conducted an additional search for known solutions in order to identify signs that match the distinctive features of the claimed device from the prototype. The search results showed that the claimed invention does not follow for a specialist explicitly from the prior art determined by the applicant. The effect of the transformations provided for by the essential features of the claimed invention on the achievement of a technical result is not revealed. In particular, the claimed invention does not provide for the following transformations: the addition of a known product with any known part, attached to it according to known rules, to achieve a technical result in respect of which the effect of such additions is established; the replacement of any part of a known product with another known part to achieve a technical result in respect of which the effect of such a replacement is established; the exclusion of any part of the funds with the simultaneous exclusion of the function due to its presence and the achievement of the usual result for such exclusion; the increase in the same type of elements to enhance the technical result due to the presence in the tool of just such elements; the implementation of a known tool or part of a known material to achieve a technical result due to the known properties of the material; the creation of a tool consisting of known parts, the choice of which and the connection between them are based on known rules, recommendations and the technical result achieved in this case is due only to the known properties of the parts of this object and the relationships between them; a change in the quantitative features or the relationship of the features, if the fact of the influence of each of them on the technical result is known and new values of the features or their relationship could be obtained from known dependencies. Therefore, the claimed invention meets the criterion of "inventive step".

The invention is illustrated by graphic materials, which depict: figure 1 is a structural diagram of a system for transmitting Quaternary-encoded radio signals; figure 2 - diagrams explaining the principle of formation of a nonlinear pseudo-random control voltage; figure 3 is a structural diagram of a frequency shift control unit; figure 4 is a structural diagram of a signal conditioner of double frequency manipulation with a variable frequency shift; 5 is a diagram illustrating the principle of the formation of a four-coded radio signal with a changing pseudo-random frequency shift; 6 is a structural diagram of a tunable signal selector; Fig.7 is a plot explaining the principle of convolution of a quaternary-encoded radio signal.

Information confirming the possibility of carrying out the invention with obtaining the above technical result are as follows.

The quad-coded radio signal transmission system shown in FIG. 1 consists of a transmitting part and a receiving part. The transmitting part contains a clock pulse generator 1, the output of which is connected to the input of the D-code generator 2, to the clock inputs of the frequency synthesizer 6, the pseudo-random number generator 7, the signal generator of double frequency manipulation with a variable frequency shift 3 and the frequency shift control unit 5. n-control outputs of the pseudo-random number generator 7, where n≥2 is an integer connected to the corresponding n-control inputs of the frequency synthesizer 6, the output of which is simultaneously connected to the modulating mod input the oscillator 4 and the information input of the frequency shift control unit 5. The output of the frequency shift control unit 5 is connected to the control input of the dual frequency shift signal driver 3. The output of the D-code generator 2 is connected to the information input of the double frequency shift signal driver with the variable frequency shift 3, the output of which is connected to the information input of the modulator 4. The output of the modulator 4 is the output of the transmitting part of the system and is connected through the path rostraneniya 8 to the input of the receiving part of the system. The receiving part of the system contains a demodulator 9, the information input of which is the input of the receiving part of the system, a clock generator 18, the output of which is connected to the clock inputs of the frequency synthesizer 16, the pseudorandom number generator 17 and the frequency shift control unit 15. In this case, the n-control outputs of the pseudorandom generator numbers 17 are connected to the corresponding n-control inputs of the frequency synthesizer 16, the output of which is simultaneously connected to the modulating input of the demodulator 9 and to the information input of the control unit frequency shift 15. The output of the frequency shift control unit 15 is connected to the control input of the tunable signal selector 10. The output of the demodulator 9 is connected to the information input of the tunable signal selector 10, the first, second, third and fourth information outputs of which are first, second, third and the fourth information inputs of the block allocating additional sequences 11. The first and second information outputs of the block allocating additional sequences 11 us to first and second data inputs of a two-channel matched filter 12, first and second information outputs of which are connected respectively to the first and second data inputs of the subtracter 13. The subtracter 13 output connected to the decision block 14, whose output is the output of the receiving part of the system.

The clock generators 1 in the transmitting part and 18 in the receiving part are identical and are designed to generate pulses of a certain duration with the required frequency f _tg = B, where B is the transmission speed of the sequence of D-code elements (technical speed), it is expressed by the number of parcels transmitted per unit of time, measured in bauds. They can be implemented, as described in the book of L.M. Goldenberg, Yu.T. Butylsky, M.X. Polyak "Digital devices on integrated circuits in communication technology" (M .: Communication, 1979, p. 72-76, fig. 3.14).

The generator of D-codes 2 is intended for the formation of a code sequence (D-code) with a period of N = 2 ^k where, N is the number of elements in a four-coded sequence; k≥2 is an integer. It can be implemented as described in A.S. No. 1177910 USSR, IPC ⁶ Н03М 5/00, declared 04/18/84, publ. 09/07/85, A.S. No. 1805550 USSR, IPC ⁶ H04L 14/00, declared 02/07/91, publ. 03/30/93 or Roland Wilson and John Richter's article “Generation and Performance of Quadraphase Welti Codes for Radar and Synchronization of Coherent and Differentially Coherent PSK” (IEEE Transactions on Communications, vol. COM-27, NO. 9, September 1979, p .1296-1301, Fig. 1).

The signal generator of double frequency manipulation with a variable frequency shift 3 is designed to generate a four-coded radio signal with a pseudo-randomly changing frequency shift. It can consist, for example, of the first 3.1 and second 3.2 varicap matrix, the first 3.3 and second 3.4 of the diode and a parallel oscillatory circuit, consisting of a capacitor 3.5 and an inductance 3.6. Moreover, the anodes of the first sections of the first 3.1 and second 3.2 varicap matrix, as well as the first tap of the parallel oscillatory circuit are jointly connected and are the output of the shaper of double frequency manipulation with a variable frequency shift 3. The anode of the second section of the first 3.1 varicap matrix is connected to the cathode of the first diode 3.3 and is the clock input of the driver of double frequency manipulation with a variable frequency shift 3. The anode of the second section of the second 3.2 varicap matrix is connected to the cathode of the second diode 3.4 and is inform the input input of the shaper of double frequency manipulation with a variable frequency shift 3. The control input of the first 3.1 and second 3.2 varicap matrix are combined and are the control input of the shaper of double frequency manipulation with a variable frequency shift 3. Anodes of the first 3.3 and second 3.4 diodes, as well as the second parallel tap oscillatory circuit jointly connected to a common ground bus.

Varicap matrices 3.1-3.2 are designed to change the frequency shift of a four-coded radio signal according to a nonlinear pseudorandom law specified by a pseudorandom number generator. They can be implemented, as described in the book of O.P. Grigoriev et al. “Diodes: A Reference Book” (M .: Radio and Communications, 1990, p.194-201, Fig. P. 46).

Diodes 3.3 and 3.4 are intended for switching the corresponding varicap matrices. They can be implemented, as described in the book of O.P. Grigoriev et al. “Diodes: A Reference Book” (M .: Radio and Communication, 1990, p.148-156, Fig. P. 4).

A parallel oscillatory circuit, consisting of a capacitor 3.5 and an inductance 3.6, is designed to generate a frequency f _{1 of the} carrier oscillation of a four-coded radio signal. It can be implemented, as described in the book by A. A. Bokunyaev et al. “The reference book of the amateur radio designer” (M .: Radio and Communication, 1990, p. 18-20, Fig. 1.9a).

Modulator 4 is designed for pseudo-random tuning of the operating frequency within the allocated frequency resource Δf = f _max -f _min , where f _max is the maximum frequency value of the allocated frequency resource; f _min - the minimum value of the frequency of the allocated frequency resource range. It can be implemented, as described in the book by N.L. Teplov, E.N. Kudelin, O.P. Lezhniuk "Non-linear radio engineering devices. Part 1 ”(M .: Military Publishing House, 1982, p.130-137, Fig.4.29).

Frequency synthesizers 6 in the transmitting part and 16 in the receiving part are identical and are intended for the formation of a pseudo-random harmonic oscillation with a frequency nominal Δf _pprch = 4f _tg (l + 1) = 4B (l + 1), where l = 0, 1, ... , L-1, L = 2 ⁿ -1 is the maximum value of the pseudo-random number in decimal calculus, n≥2 is the number of controlled inputs of the frequency synthesizer. They can be implemented as described in RF patent No. 2208915, IPC ⁷ H04K 3/00, the application. 11/04/02, publ. 07.20.03, Bull. No. 20.

, где ΔF_c=4B - эффективная ширина спектра четверично-кодированного радиосигнала;

- меньшее целое число. Они могут быть реализованы, как описано в книге У.Тице, К.Шенк «Полупроводниковая схемотехника» (M.: Мир, 1982, с.356-359, рис.20.20) или в книге Г.И.Тузова и др. «Помехозащищенность радиосистем со сложными сигналами» (M.: Радио и связь, 1985, с.27-34, рис.2.4).The pseudo-random number generators 7 in the transmitting part and 17 in the receiving part are identical and are designed to generate pseudo-random numbers l = 0, 1, ..., L-1 in binary terms, where the maximum pseudo-random number L depends on the allocated frequency resource Δf and is determined in decimal form as follows

where ΔF _c = 4B is the effective spectrum width of the four-coded radio signal;

is a smaller integer. They can be implemented as described in the book by W. Tice, K. Schenk “Semiconductor circuitry” (M .: Mir, 1982, p. 356-359, Fig. 20.20) or in the book of G.I. Tuzov and others. “ Interference immunity of radio systems with complex signals ”(M .: Radio and communication, 1985, pp. 27-34, Fig. 2.4).

The frequency shift control units 5 in the transmitting part and 15 in the receiving part are identical and are designed to generate a nonlinear pseudo-random control voltage. They can consist, for example, of a low-pass filter 5.1, a frequency detector 5.2 and a frequency divider with a division factor of four 5.3. The input of the frequency divider with a division factor of four 5.3 is the information input of the frequency shift control unit 5. The output of the frequency divider with a division factor of four 5.3 is connected to the information input of the frequency detector 5.2, the clock input of which is the clock input of the frequency shift control unit 5. Output of the frequency detector 5.2 is connected to the input of the low-pass filter 5.1, the output of which is the output of the frequency shift control unit 5.

The low-pass filter 5.1 is designed to highlight a useful pseudo-random control voltage U _CPR (l) with a low level of side vibrations. It can be implemented, as described in the book by A.F. Beletsky, “Fundamentals of the Theory of Linear Electric Circuits” (Moscow: Svyaz, 1967, p. 591-596, fig. 21.36, fig. 21.37).

The frequency detector 5.2 is intended for the formation of a nonlinear pseudo-random control voltage U _CPR (l), which depends on the degree of difference in the frequencies of the compared oscillations. It can be implemented, as described in the book by N.L. Teplov, E.N. Kudelin, O.P. Lezhniuk "Non-linear radio engineering devices. Part 1 ”(M .: Military Publishing House, 1982, p.178-198, Fig.5.47).

. Он может быть реализован, как описано в книге Манассевич В. «Синтезаторы частот (Теория и проектирование)» (М.: Связь, 1979, с.260-271 рис.6.24).A frequency divider 5.3 with a division factor of four is designed to reduce the frequency of a nonlinear pseudo-random control harmonic oscillation to the desired value

. It can be implemented as described in the book by Manassevich V. “Frequency Synthesizers (Theory and Design)” (Moscow: Communication, 1979, pp. 260-271, Fig. 6.24).

The propagation path 8 is intended for the distribution of a four-coded radio signal. The basis of the propagation path is one or another medium in which the signal propagates, for example, in electrical communication systems - this is a cable or waveguide, in radio communication systems - the area of space in which electromagnetic waves propagate.

The demodulator 9 is designed to eliminate pseudo-random tuning of the operating frequency within the allocated frequency resource. It can be implemented, as described in the book by N.L. Teplov, E.N. Kudelin, O.P. Lezhniuk "Non-linear radio engineering devices. Part 1 ”(Moscow: Military Publishing House, 1982, p.130-137, Fig.4.29).

A tunable signal selector 10 is designed to select a quad-coded radio signal. It can consist, for example, of the first 10.1, second 10.2, third 10.3 and fourth 10.4 tunable bandpass filters. The information inputs of the first 10.1, second 10.2, third 10.3 and fourth 10.4 tunable bandpass filters are combined and are the information input of the tunable signal selector 10. Moreover, the controlled inputs of the first 10.1, second 10.2, third 10.3 and fourth 10.4 tunable bandpass filters are also combined and are the control input tunable signal selector 10. The outputs of the first 10.1, second 10.2, third 10.3 and fourth 10.4 tunable bandpass filters are respectively the first, second, third and fourth The erased information outputs of the tunable signal selector 10.

Tunable band-pass filters 10.1-10.4 are designed for frequency selection of a strictly defined radio signal with a pseudo-randomly changing frequency shift. They can be implemented using the variable bandwidth adjustment, for example, as described in the book by A. A. Bokunyaev et al. “The reference book of the amateur radio designer” (Moscow: Radio and Communication, 1990, p. 72-74, Fig. 2.82).

The block for extracting additional sequences 11 is intended for extracting the first additional sequence from the odd elements of the quaternary-encoded sequence (extraction of elements α, β) and extracting the second additional sequence from the even elements of the quadruply-encoded sequence (extraction of elements γ, δ). It can be implemented as described in the patent of the Russian Federation No. 2188516, IPC ⁷ H04L 27/26, decl. 05.21.01, publ. 08/27/02, Bull. Number 24.

A two-channel matched filter 12 is designed to convolve additional sequences up to the duration of one element of a four-coded sequence. It can be implemented as described in A.S. No. 1721837 USSR, IPC ⁶ H04L 27/26, declared 01/08/90, publ. 03/23/92.

Subtractor 13 is designed to subtract the negative voltage pulse supplied to its second input from the positive voltage pulse supplied to its first input. It can be implemented, as described in the book by W. Tice, K. Schenk “Semiconductor circuitry” (M .: Mir, 1982, p. 137-138, Fig. 11.2).

The decision block 14 is designed to decide on the transmitted Quaternary-coded sequence. It can be implemented on the basis of the comparator, as described in the book of W. Tice, K. Schenk “Semiconductor circuitry” (M .: Mir, 1982, pp. 76-77, Fig. 6.13).

The system for transmitting Quaternary-encoded radio signals, presented in figure 1, operates as follows.

When you turn on the system in the transmitting part, the clock generator 1 with a frequency f _tg generates a sequence of clock pulses with a duty cycle equal to two, presented on the diagrams of figa. Each element of this sequence with a high level of "1" will be considered odd, and with a low level of "0" - even. The sequence of clock pulses (Fig. 2 a) from the clock generator 1 simultaneously arrives at the clock inputs of the signal generator of double frequency manipulation with a variable frequency shift 3, the frequency shift control unit 5, the frequency synthesizer 6 and the pseudo random number generator 7, and also to the input of the shaper D-codes 2.

In the generator of D-codes 2 according to clock pulses (Fig. 2a), the corresponding initial quaternary-encoded sequence with a period N = 2 ^k that does not have side outliers in the aperiodic autocorrelation function (ACF), for example, Velty or E codes, is generated and cycled codes.

As an example, the diagrams of FIG. 2b show a cyclic implementation of the following quaternary-encoded sequence αγαδαγβγ generated in the D-code generator 2 with the number of elements N = 8. The quaternary encoded sequence contains the following elements: α, β, γ, δ, where: α, β transmit the odd elements of the D code, and γ, δ the even elements of the D code. From the output of the generator of D-codes 2, the generated (Fig.2b) four-coded sequence is fed to the information input of the signal generator of double frequency manipulation with a variable frequency shift 3.

In the pseudo-random number generator 7, the sequence of clock pulses (Fig. 2a) is converted into a nonlinear pseudorandom sequence, which has a high structural secrecy. The nonlinear pseudorandom number generated in the pseudo-random number generator 7 is supplied simultaneously to the n-control outputs of the pseudo-random number generator 7 with a time shift of one clock cycle at each output of the pseudo-random number generator 7. The pseudo-random number generator 7 has a bit capacity of L = 2 ⁿ -1 in depending on the allocated frequency resource Δf. As an example, the diagrams of FIGS. 2c, d show the implementation of a nonlinear pseudo-random sequence in binary form generated in the pseudo-random number generator 7 with values L = 3, l = 0, 1, ..., L-1 and n = 2.

A nonlinear pseudo-random sequence in binary form with n-control outputs, where n≥2 is the number of outputs of the pseudo-random number generator 7, is supplied respectively to the n-control inputs of the frequency synthesizer 6, where n≥2 is the number of control inputs of the frequency synthesizer 6. To the clock input frequency synthesizer 6 receives a sequence of clock pulses (figa) with a frequency f _tg from the output of the clock generator 1.

In the frequency synthesizer 6, a nonlinear pseudo-random harmonic oscillation is formed with a nominal value Δf _pprh (l) = 4B (l + 1) with a random frequency shift depending on the nominal value of the pseudo-random number l, supplied in binary code to the n-control inputs of the frequency synthesizer 6. As example on the diagrams of fig.2d presents the implementation of non-linear pseudo-random harmonic oscillation Δf _pprh (l), depending on the nominal value of the pseudo-random number l in the binary code generated in the synthesizer often 6 with values L = 3, l = 0, 1, ..., L -1 and n = 2. Formed in the frequency synthesizer 6, a nonlinear pseudo-random harmonic oscillation with a nominal value Δf _pprh (l) (Fig.2d) is simultaneously fed to the information input of the frequency shift control unit 5 and the modulating input of the modulator 4.

(фиг.2д) в четыре раза и формирование управляющего нелинейного псевдослучайного гармонического колебания f_упр(l)=B(l+1), зависящего от номинала псевдослучайного числа l в двоичной форме. Сформированное на выходе делителя частоты с коэффициентом деления на четыре 5.3 управляющее нелинейное псевдослучайное гармоническое колебание f_упр(l) поступает на информационный вход частотного детектора 5.2, а на тактовый вход частотного детектора 5.2 поступает последовательность тактовых импульсов (фиг.2а) с частотой f_тг с генератора тактовых импульсов 1. В частотном детекторе 5.2 происходит сравнение управляющего нелинейного псевдослучайного гармонического колебания f_упр(l) с частотой генератора тактовых импульсов 1 f_тг, (фиг.2а). На выходе частотного детектора 5.2 формируется нелинейное псевдослучайное управляющее напряжение U_упр(l) которое зависит от степени расхождения частот сравниваемых колебаний в соответствии с выражениемThe structural diagram of the frequency shift control unit 5 (15) is shown in FIG. Nonlinear pseudo-random harmonic oscillation Δf _frf (l) (Fig.2d) from the output of the frequency synthesizer 6 is fed to the information input of the frequency shift control unit 5, which is the input of the frequency divider with a division factor of four 5.3. In a frequency divider with a division factor of four 5.3, the frequency of a nonlinear pseudo-random harmonic oscillation decreases

(2E) four times and the formation of the control pseudorandom nonlinear harmonic oscillation _exercise f (l) = B (l + 1) depending on the nominal pseudo-random number l in binary form. Formed at the output of the frequency divider with a division factor of four 5.3, the control non-linear pseudo-random harmonic oscillation f _control (l) is fed to the information input of the frequency detector 5.2, and a sequence of clock pulses (Fig.2a) with a frequency f _tg s clock generator 1. In the frequency detector 5.2, the control non-linear pseudo-random harmonic oscillation f _control (l) is compared with the frequency of the clock generator 1 f _tg , (figa). At the output of the frequency detector 5.2, a nonlinear pseudorandom control voltage U _control (l) is formed which depends on the degree of difference in the frequencies of the compared oscillations in accordance with the expression

_Ex Δf (l) = f _simp (l) -f _n = B (l + 1) -B = Bl.

As an example, on the diagrams of FIG. 2e, the implementation of a nonlinear pseudo-random control voltage U _control (l), depending on the nominal value of the pseudo-random number l in binary form, generated in the frequency detector 5.2 with values L = 3, l = 0, 1, ... , L-1 and n = 2.

Formed in the frequency detector 5.2 non-linear pseudo-random control voltage U _CPR (l) (Fig.2E) is fed to the input of the low-pass filter 5.1. The low-pass filter 5.1 should provide a significant weakening of side Raman oscillations, therefore, to obtain a pseudo-random control voltage U _CPR (l) (Fig.2e) with a low level of side oscillations. From the output of the lower filter, often 5.1, a nonlinear pseudo-random control voltage U _control (l) formed in the frequency detector 5.2 is supplied to the control input of the signal generator of double frequency manipulation with a variable frequency shift 3.

The structural diagram of the signal generator double frequency manipulation with a variable frequency shift 3 is presented in figure 4. In the double-frequency manipulation signal former with a variable frequency shift 3, the four-coded sequence (Fig.2b) generated in the D-code former 2 is converted into a four-coded radio signal. The change in the high-frequency oscillations of the quaternary-encoded radio signal generated in the driver of signals of double manipulation with a variable frequency shift 3, can be described, as presented in table. 1 (excluding the effects of non-linear pseudo-random control voltage U _CPR (l) (fig.2e)):

Table 1 Quaternary Coded Elements Clock input of block 3 (from block 1) Information input of block 3 (from block 2) Quadruple Coded Radio Frequency δ 0 0 f ₁ γ 0 one f ₂ β one 0 f ₃ α one one f ₄

,

,

- частотный сдвиг между частотными каналами четверично-кодированного радиосигнала; Δf₁=xB, Δf₂=mB, Δf₃=zB; x≥1, m≥1, z≥1 - коэффициенты, управляющие изменением частотного сдвига между частотными каналами четверично-кодированного радиосигнала.where: f ₁ <f ₂ <f ₃ <f ₄ or f ₁ > f ₂ > f ₃ > f ₄ is the frequency dependence of the frequency channels of the four-coded radio signal;

,

,

- the frequency shift between the frequency channels of the four-coded radio signal; Δf ₁ = xB, Δf ₂ = mB, Δf ₃ = zB; x≥1, m≥1, z≥1 - coefficients that control the change in the frequency shift between the frequency channels of the four-coded radio signal.

As an example, the diagrams of FIG. 5a show the implementation of a quaternary-encoded radio signal, and the diagrams of FIG. 5b shows the time-frequency implementation of a quadruple-encoded radio signal generated in a signal generator of double frequency manipulation with a variable frequency shift of 3 at values of U _control (l) = 0, x = m = z = 1 and Δf ₁ = Δf ₂ = Δf ₃ .

The oscillation frequency of the oscillator of the driver of the signal generator of double frequency manipulation with a variable frequency shift 3 is made by connecting with the help of diodes 3.3 and 3.4 varicap matrixes 3.1 and 3.2 to a parallel oscillatory circuit (3.5-3.6). The varicap matrix 3.1 and / or 3.2 are connected when they arrive at the clock input and / or information input of the signal generator of double frequency manipulation with a variable frequency shift of 3 pulses of negative polarity, respectively. The nonlinear pseudo-random control voltage U _control (l) (Fig. 2e) from the control input of the signal generator of double frequency manipulation with a variable frequency shift 3 simultaneously enters the control inputs of the first 3.1 and second 3.2 varicap matrices, where under the influence of a nonlinear pseudo-random control voltage U _control ( l) (fig. 2e) the capacitance of the first 3.1 and second 3.2 varicap matrixes changes. By changing the capacitance of the first 3.1 and second 3.2 varicap matrices, the total capacitance of the parallel oscillatory circuit (3.5-3.6) of the oscillator of the driver of the signal of double frequency manipulation with a variable frequency shift 3 changes, as a result, the frequency shift between the frequency channels of the quad-coded radio signal changes in accordance with the expression

Δf _sdv (U _control (l)) = Δf _sdv + ΔF (U _control (l)),

where Δf _sdv = B is the standard frequency shift between the frequency channels of the quad-coded radio signal, depending on the speed of transmission of a sequence of elements of the D-code; ΔF (U _CPR (l)) is a nonlinear pseudo-random frequency increment to the standard frequency shift between the frequency channels of the quad-coded radio signal, depending on the value of the nonlinear pseudo-random control voltage U _CPR (l) (Fig. 2e).

As an example, the diagrams of FIG. 5c show the implementation of a nonlinear pseudo-random frequency increment ΔF (U _cfr (l)) generated in the driver of signals of double frequency manipulation with a variable frequency shift 3 depending on the magnitude of the nonlinear pseudo-random control voltage U _cfn (l) (Fig .2e) for L = 3, l = 0, 1, ..., L-1 and n = 2.

,

,

- частотный сдвиг между частотными каналами четверично-кодированного радиосигнала, зависящий от величины нелинейного псевдослучайного управляющего напряжения U_упр(l) (фиг.2е); Δf₁(U_упр(l))=x(l)B, Δf₂(U_упр(l))=m(l)B, Δf₃(U_упр(l))=z(l)B;

- коэффициент частотного сдвига, зависящий от величины нелинейного псевдослучайного управляющего напряжения U_упр(l) (фиг.2е).Thus, a signal shaper double FSK variable frequency offset 3 under the influence of the generated pseudorandom nonlinear control voltage U _simp (l) (2e) is formed by the quaternary-coded signal is with different values of the frequency shift Δf _sh (U _simp (l)) between the frequency channels of a quad-coded radio signal, where

,

,

- the frequency shift between the frequency channels of the four-coded radio signal, depending on the magnitude of the nonlinear pseudorandom control voltage U _CPR (l) (Fig. 2e); Δf ₁ (U _control (l)) = x (l) B, Δf ₂ (U _control (l)) = m (l) B, Δf ₃ (U _control (l)) = z (l) B;

- the coefficient of the frequency shift, depending on the magnitude of the nonlinear pseudo-random control voltage U _CPR (l) (Fig.2E).

At the output of the driver of signals of two-fold frequency manipulation with a variable frequency shift 3 for the values x (l) ≠ m (l) ≠ z (l) and Δf ₁ (U _control (l)) ≠ Δf ₂ (U _control (l)) ≠ Δf ₃ (U _control (l)) a four-coded radio signal is generated according to the following rule:

where f _n = f _min is the frequency of the carrier oscillations of the four-coded radio signal corresponding to the minimum frequency value of the allocated frequency resource; U _c is the amplitude of the unmodulated element of the four-coded radio signal.

As an example, the diagrams of FIG. 5g show the time-frequency implementation of a quadruple-encoded radio signal generated in a signal generator of double frequency manipulation with a variable frequency shift of 3 at values of x (l) ≠ m (l) ≠ z (l) and Δf ₁ ( U _control (l)) ≠ Δf ₂ (U _control (l)) ≠ Δf ₃ (U _control (l)).

The four-coded radio signal generated in the driver of double frequency manipulation with a variable frequency shift 3 (Fig. 5d) is fed to the information input of the modulator 4, which is the output of the transmitting part of the system, and the non-linear pseudorandom harmonic formed in the frequency synthesizer 6 is fed to the modulating input 4 fluctuation with a nominal value Δf _pprc (l) (fig.2d). At the output of modulator 4, with values of x (l) ≠ m (l) ≠ z (l) and Δf ₁ (U _cfr (l)) ≠ Δf ₂ (U _cfn (l)) ≠ Δf ₃ (U _cfn (l)) a four-coded radio signal with frequency hopping is generated within the allocated frequency resource Δf according to the following rule:

As an example, in the diagrams of Fig. 5d, the time-frequency implementation of a quadruple-coded RF signal from the frequency hopping signal generated in modulator 4 is presented for the values x (l) ≠ m (l) ≠ z (l) and Δf ₁ (U _control (l)) ≠ Δf ₂ (U _control (l)) ≠ Δf ₃ (U _control (l)).

The four-coded radio signal (Fig.5d), formed in the transmitting part of the system, enters the propagation path 8.

Having passed through the propagation path 8, the four-coded radio signal (Fig.5d) is fed to the information input of the demodulator 9, which is the input of the receiving part of the system.

The clock generator 18, the pseudo-random number generator 17 and the frequency synthesizer 16 of the receiving part of the system work and form a nonlinear pseudo-random harmonic oscillation with a nominal value Δf _pprh (l) (Fig.2d) similarly to the transmitting part of the system. Therefore, at the output of the frequency synthesizer 16, a nonlinear pseudorandom harmonic oscillation with a nominal value Δf _pprh (l) is generated (Fig.2d), which is fed to the modulating input of the demodulator 9.

In the demodulator 9, due to the frequency synthesizer 16, the pseudorandom numbers controlled by the generator 17, the jumps in the operating frequency Δf _pfp (l) are eliminated, as a result, the information symbols of the four-coded radio signal are transferred to the original selected frequencies.

The control unit of the frequency shift 15 of the receiving part of the system operates and generates a nonlinear pseudo-random control voltage U _control (l) (Fig.2E) similarly to the transmitting part of the system. Therefore, at the output of the frequency shift control unit 15, a non-linear pseudo-random control voltage U _control (l) is generated (Fig. 2e), which is fed to the control input of the tunable signal selector 10.

From the output of the demodulator 9, the four-coded radio signal is fed to the input of the tunable signal selector 10, which performs frequency selection of strictly defined high-frequency elements of the four-coded radio signal (Fig. 5a). The block diagram of the tunable signal selector is presented in Fig.6. The four-coded radio signal (Fig. 5a) is simultaneously fed to the information inputs of the first 10.1, second 10.2, third 10.3 and fourth 10.4 tunable bandpass filters, and the non-linear non-linear input to the controlled inputs of the first 10.1, second 10.2, third 10.3 and fourth 10.4 tunable bandpass filters pseudo-random control voltage U _control (l) (Fig.2E) from the output of the frequency shift control unit 15.

In the first 10.1, second 10.2, third 10.3 and fourth 10.4 tunable band-pass filters, the nonlinear pseudo-random control voltage U _control (l) (Fig.2e) changes the capacitance of the varicaps. Thus, the passband of the first 10.1, second 10.2, third 10.3 and fourth 10.4 tunable bandpass filters is tuned in accordance with the change in the frequency shift Δf _sdv (U _control (l)) between the frequency channels of the quad-coded radio signal, and the frequency selection of strictly defined elements of a four-coded radio signal.

At the outputs of the first 10.1, second 10.2, third 10.3, and fourth 10.4 tunable bandpass filters with values of x (l) ≠ m (l) ≠ z (l) and Δf ₁ (U _control (l)) ≠ Δf ₂ (U _control (l )) ≠ Δf ₃ (U _control (l)) a four-coded radio signal is generated according to the following rule:

As an example, the diagrams of FIGS. 7a, b, c, d show realizations of the generated first, second, third and fourth high-frequency radio signals, respectively.

The first, second, third and fourth high-frequency radio signals (figa, b, c, d) from the corresponding outputs of the tunable signal selector 10 respectively arrive at the first, second, third and fourth inputs of the block for extracting additional sequences 11.

In the block for extracting additional sequences 11, the envelope is extracted from the first, second, third and fourth high-frequency radio signals (Fig. 7a, b, c, d) and the elimination of the carrier high-frequency oscillations. At the first and second information outputs of the block for extracting additional sequences 11, the first and second additional sequences are respectively formed. As an example, on the diagrams of FIG. 7e, g shows the implementation of the generated first and second additional sequences, respectively. In this case, the first additional sequence (Fig.7d) is formed from the odd elements of the quaternary-encoded sequence (allocation of elements α, β), and the second additional sequence (Fig.7g) is formed from the even elements of the quaternary-encoded sequence (selection of elements γ, δ) . The formed first and second additional sequences (Fig.7d, g) from the corresponding information outputs of the block for extracting additional sequences 11, respectively, are supplied to the first and second information inputs of a two-channel matched filter 12.

и

означает увеличение амплитуды сигналов

и

в 4 раза, так как, для примера, k=3. Свернутые первая и вторая дополнительные последовательности (фиг.7з, и) с соответствующих информационных выходов двухканального согласованного фильтра 12 соответственно поступают на первый и второй информационные входы вычитателя 13.In the dual channel matched filter 12, first and second complementary sequences (fig.7d, x) to fold the duration of one element of the quaternary-coded sequences, as the voltage becomes larger at 2 ^k-1 times the amplitude element of the quaternary-coded sequence. As an example, the diagrams in figs, and presents the implementation of the folded first and second additional sequences, respectively, where

and

means an increase in signal amplitude

and

4 times, since, for example, k = 3. The folded first and second additional sequences (FIGS. 7h, i) from the corresponding information outputs of the two-channel matched filter 12 respectively arrive at the first and second information inputs of the subtractor 13.

Subtractor 13 provides the subtraction of a negative pulse (Fig.7i) with a voltage of 2 ^k-1 supplied to its second information input from a positive pulse (Fig.7z) with a voltage of 2 ^k-1 supplied to its first information input. Therefore, at the output of the subtractor 13 pulses of a folded four-coded sequence with a voltage of 2 ^k times the amplitude of the element of the four-coded sequence will be generated. As an example, the diagrams of FIG. 7y show an implementation of a folded quadruple-encoded sequence. As a result, a convolution of a quaternary-coded sequence (Welty codes or E-codes) is carried out, characterized in that it does not have side outliers in an aperiodic ACF.

At decision block 14, a decision is made on the transmitted quaternary-coded sequence.

Thus, the proposed quadruple-coded radio signal transmission system provides an extension of the field of application due to increased noise immunity and reliability under the influence of intentional imitating interference (coinciding with the structure of the useful signal) in communication channels with random signal parameters (phase, amplitude and polarization) of the meter and decameter wavelength ranges with frequency hopping without extending the frequency resource and reducing the system throughput due to a pseudo-random change in the frequency on the shift between the frequency channels of a quadruple-encoded radio signal, and is intended for synchronous and asynchronous communication systems in the transmission of discrete information and synchronization.

The above information indicates the following conditions are met when using the claimed device:

- a tool embodying the claimed device in its implementation, is intended for use in synchronous and asynchronous communication systems as a transmission of discrete information and synchronization;

- for the claimed device in the form described in the claims, the possibility of its implementation using the means and methods described in the application or known prior to the priority date is confirmed;

- a tool embodying the claimed invention in its implementation, is able to ensure the achievement of perceived by the applicant technical result.

Thus, the claimed invention meets the criterion of "industrial applicability".

Claims (4)

1. A system for transmitting quadruple-coded radio signals, containing in the transmitting part a clock pulse generator, the output of which is connected to the input of the D-code generator, to the clock inputs of a frequency synthesizer and a pseudorandom number generator, whose n-control outputs, where n≥2 is an integer are connected to the corresponding n-control inputs of the frequency synthesizer, the output of which is connected to the modulating input of the modulator, the output of the modulator is the output of the transmitting part of the system and connected through the propagation path to the input the volume of the system, the receiving part of the system includes a demodulator, the information input of which is the input of the receiving part of the system, a clock pulse generator, the output of which is connected to the clock inputs of the frequency synthesizer and pseudorandom number generator, the n-control outputs of which are connected to the corresponding n-control inputs of the frequency synthesizer the output of which is connected to the modulating input of the demodulator, the first and second information outputs of the block for additional sequences allocation are connected respectively to the first and second information inputs of a two-channel matched filter, the first and second information outputs of which are connected respectively to the first and second information inputs of the subtractor, the output of the subtractor is connected to a decision block, the output of which is the output of the receiving part of the system, characterized in that in the transmitting part of the system additionally introduced a signal shaper of double frequency manipulation with a variable frequency shift and a frequency shift control unit, the output of the generator and clock pulses are also connected to the clock inputs of the signal generator of double frequency manipulation with a variable frequency shift and to the frequency shift control unit, and the output of the frequency synthesizer is also connected to the information input of the frequency shift control unit, the output of which is connected to the control input of the signal generator of double frequency manipulation with variable frequency shift, and the output of the shaper D-codes connected to the information input of the shaper signals double frequency manipulator a variable frequency shift, the output of which is connected to the information input of the modulator, and a tunable signal selector and a frequency shift control unit are additionally introduced into the receiving part of the system, while the output of the clock generator is also connected to the clock input of the frequency shift control unit, and the output of the frequency synthesizer connected to the information input of the frequency shift control unit, the output of which is connected to the control input of the tunable signal selector, the demodulator output under for prison to the data input of the tunable selector signal, the first, second, third and fourth data outputs of which are respectively the first, second, third and fourth information inputs of the block for additional sequences. 2. The transmission system according to claim 1, characterized in that the driver of signals of double frequency manipulation with a variable frequency shift consists of a first and second varicap matrix, a first and second diode, as well as a parallel oscillatory circuit, consisting of a capacitor and inductance, while the anodes the first sections of the first and second varicap matrix, as well as the first tap of the parallel oscillatory circuit are jointly connected and are the output of the shaper of double frequency manipulation with a variable frequency shift, the anode of the second section of the first varicap matrix is connected to the cathode of the first diode and is the clock input of the shaper of double frequency manipulation with a variable frequency shift, and the anode of the second section of the second varicap matrix is connected to the cathode of the second diode and is the information input of the shaper of double frequency manipulation with a variable frequency shift, inputs the controls of the first and second varicap matrix are jointly connected and are the control input of the shaper of double frequency manipulation with changing by direct frequency shift, the anodes of the first and second diode, and a second branch of the parallel oscillating circuit together connected to a common ground bus. 3. The transmission system according to claim 1, characterized in that the frequency shift control unit consists of a low-pass filter, a frequency detector and a frequency divider with a division factor of four, the input of which is the information input of the frequency shift control unit, the output of the frequency divider with a division coefficient four connected to the information input of the frequency detector, the clock input of which is the clock input of the frequency shift control unit, the output of the frequency detector is connected to a low-pass filter, the output to torogo is the output frequency shift of the control unit. 4. The transmission system according to claim 1, characterized in that the tunable signal selector consists of the first, second, third and fourth tunable bandpass filters, the information inputs of which are combined and are the information input of the tunable signal selector, while the controlled inputs of the first, second, third and the fourth tunable bandpass filters are also combined and are the control input of the tunable signal selector, and the outputs of the first, second, third and fourth tunable polo ovyh filters are respectively first, second, third and fourth data outputs of the tunable signal selector.

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