RU1800385C - Method of phase detection - Google Patents

Abstract

Usage: it is intended for measuring and monitoring parameters of various nature and can be used in communication and telemetry systems, as well as for measuring and monitoring the values of the reactive and active components of the changing impedance of devices and sensors. SUMMARY OF THE INVENTION: during phase detection, an action signal and reference coherent signals are generated, the phase-shifted measured signal is multiplied, the phase of which is changed proportionally to the measured parameter value, and the reference quadrature signals are measured, the separation and the quadrature parts of the measured signal are measured, and the quadrature phase shift is performed reference signals at an angle of 360 ° / N0n, where N0n is a number selected according to the required measurement accuracy, the difference is that the non-generated signal of exposure is distributed over time In the DF directions, they form an absolutely coherent quasi-analog sinusoidal signal with the number of PCF quantization levels from it, they change the amplitude of the first half-wave Vmi of the quasi-analogue sinusoidal signal, if its phase is shifted up or down and / or up the magnitude of the amplitude of the second half-wave of the quasi-analogue sinusoidal signal, and if the phase is shifted to the leading side, a change is made in the direction of increasing the amplitude of the first half-wave of the quasianalogue analog sinusoidal signal and / or in the direction of decreasing the amplitude of the second half-wave Vm2 of this signal by Vmi / Nb and Vm2 NB, respectively, where Mb is the number of changes in Vmi and Vm2, after which similar operations are performed on any of the indicated half-wave amplitudes the formation of completely coherent, shifted by different values of fixed phases, several reference quasicontinuous signals at the vertices, then these signals are phase shifted by changing the beginning of the distribution of the signal of influence and th e measured signal without destroying the coherence, regardless of their frequency, until a zero value of the detected signals. 4 ill. from 00 to about to 00 eat

Description

The invention relates to radio engineering, is intended for the measurement and control of parameters of various nature and can be used in automatic control and telecontrol systems of moving and manipulating

devices and processes of various natures, in radio, optical and acoustic location, in communication and telemetry systems, as well as for measuring the control of reactive and active components of the changing impedance of devices and sensors or wave propagation index in the medium.

The purpose of the invention is the expansion of the scope, increasing the speed and accuracy of phase detection.

The essence of the invention lies in the fact that according to the phase detection method, an influence signal Ui and reference coherent signals U2 and Us are generated, phase detection is performed, multiplying the phase-shifted measured response signal 1M, the phase of which is changed proportionally to the value of the measured parameter Ax , with the reference signal and with a 90 ° phase-shifted quadrature reference signal, the in-phase and quadrature parts of the measured response signal are measured with respect to the corresponding reference signal, phase shift o of the reference signal and the phase of the quadrature reference signal at an angle equal to 360 ° / N0n, where Non is the number selected by the required measurement accuracy for the reference signal, in contrast to the prototype, the generated 1M exposure signal is distributed in time in the pdf directions and from the distributed signal the effects form an absolutely coherent quasi-analogue sinusoidal signal with the number of quantization levels of the PCF, change the amplitude of the first half-wave Vmi of the quasi-analogue sinusoidal signal, if the the phase of the measured signal is shifted in the direction of lagging relative to the phase of the reference signal or (and) in the direction of increasing the amplitude of the second half-wave of this signal, and if the phase of the generated quasi-analogue sinusoidal signal is shifted in the direction of advance relative to the phase of the reference signal increasing the amplitude of the first half-wave of the quasi-analog sinusoidal signal and (or) in the direction of decreasing the amplitude of the second half-wave Vm2 of this signal, respectively, by -rjr- and Vm2 NB, where

the number of necessary changes in the amplitude of the corresponding half-wave Vmi, Vm2, after which, on any of the indicated changes in one of the half-wave amplitudes, the operations of forming completely coherent, shifted by different values of fixed phases, several reference quasicontinuous signals at the vertices are carried out, then phase shifts of these signals by changing the beginning of the distribution of the exposure signal and the generated measured signal without destroying the coherence, regardless of their frequency until a measurement is made corresponding to the zero voltage value of the detected signal.

Figure 1 shows a block diagram of an implementation of a phase detection method; in FIG. 2 is a circuit diagram of a signal distributor; Fig. 3 is a schematic diagram of a driver of variable amplitude half-wave and phase signals; Fig. 4 is a schematic diagram of a driver of fully coherent quadrature reference signals of an alternating phase.

A device (one of the options) that implements the proposed method of phase detection (Fig. 1) comprises a reference generator 1, a shaper 2 of coherent quadrature reference signals of a variable phase, a phase sensor 3, phase detectors 4 and 5, an integrator-converter 6, a signal distributor 7 , driver 8 of variable amplitude-half-wave and phase signals, switch 9. Information outputs of the integrator-converter 6, which are information outputs 10 and 11 of the device, as well as control inputs for phase control formulator 2 and for controlling the amplitudes of the half-waves and the phase of the shaper 8, which are the control inputs 12 and 13 of the device.

The method does not exclude, but makes it possible to connect the information output 10 to the control input 13 to improve the dynamic properties of a device that implements the proposed method.

The external inputs can be connected to the control inputs and information outputs of the device.

In Fig. 2, are indicated: Pi is a bit counter 14 and its decoder 15 with 2Pi and discrete outputs.

In Fig. 3, the following are indicated: trigger memory register 16 with multi-bit control input 13 NB and with pdf groups P2 - bit outputs; pdf logical keys 17 and the corresponding number of weight resistor dividers 18; adder 19 pcf quanta for each of the pdf discs.

In Fig. 4, the following are indicated: P-bit counter 20 with non-bit control input 12 Non and its decoder 21 with discrete outputs; driver 22 quadrature reference signal containing fixed cosine quadrature-weight resistor dividers 23 and

adder 24 quanta; a common-mode reference signal shaper 25 comprising sinus-fixed in-phase weight resistor dividers 26 and a quantum adder 27.

The device includes blocks:

- the reference oscillator 1 is designed to generate a highly stable clock frequency signal Ui and is made, for example, according to the usual oscillator circuit of the oscillator, the output of which is connected to the counting inputs of the counters 14 and 20, respectively, of the distributor 7 and the driver 2;

- a shaper 2 of completely coherent quadrature reference signals of a variable phase (Fig. 4) is designed to generate completely coherent, according to the model, with each other and with respect to the common-mode U2 and quadrature 11s signals, quantized at clock frequencies, binary reference signals with quasi-continuous vertices , the phase of which simultaneously changes in proportion to the decimal weight of the Non control code fed to the multi-bit P-input of the counter 20 of the shaper 2, which provides storage the quadrature and complete (without the introduced error e) coherence of the reference signals in the entire range of phase changes and regardless of the frequency of the impact signal Ui, while the output of the counter 20 through the decoder 21 is connected respectively through the dividers 23 to the adder 24 of the former 22, and through the dividers 26 to the adder 27 of the shaper 25, the outputs of the adders 24 and 27 of the shaper 2 are connected to the key inputs 2 of the quadrature detector 5 and in-phase detector 4, respectively;

- the phase sensor 3 is a multipole, the phase shift and attenuation introduced by it must be monitored, measured, and which can be either the parameters of the sensor 3 itself or the parameter of an external action of one nature or another on the sensor via the control input Ax or direct influence of the composition and processes of the medium of the propagation of the exposure signal Us, while the exposure signal is fed to the signal input of the phase sensor from the output of the adder 19 of the shaper 8 (Fig. 3) of variable amplitude half-waves x phase signals, and the indicative output of the phase sensor is connected to the analog inputs of 1 phase detectors 4 and 5;

- phase detector 4 (5) is intended (each) for converting the difference in amplitudes of the bi-directional half-waves of the quasi-analog response signal 1M supplied to the analog inputs 1 of detectors 4 and 5, and (or) the phase difference of the multiplied signal

response and reference signals U2 and Uz, with quasicontinuous vertices, each arriving at the inputs of 2 detectors 4 and 5, respectively, in quadrature with respect to each other - at the voltages of complex phases, respectively, U1 and U1e, applied to the inputs of integrators 33 of integrator-converter 6, at This phase detector is made according to a well-known scheme, for example, an annular phase detector containing 5 semiconductor triodes as non-linear elements, the emitters of which are connected together for a common load, collectors through a paraphase splitting frames are connected to the sensor 3, and

0 the bases of these triodes are connected, one with the key input 2 of detector 4 (5); friend - with a source of displacement;

- integrator-converter 6 is designed for filtering, smoothing and

5 converting the voltage of a complex shape into a constant component of the DC voltage extracted during a period in a digital form convenient for measurement and processing;

0 - signal distributor 7 is designed to distribute in time, using the Pi-bit counter 14 and its decoder 15, in the pdf the directions of the impact signal Ui in the form, for example, of the potential intervals of the repetition periods of the generated impact signal, while the multiposition output of the decoder 15 the distributor 7 is connected each in a counting order of positions to the first RE

0 to the inputs of the corresponding PDF of the two-input logic keys 17 of the driver 8 (Fig. 3), and the counting input of the counter 14 is connected to the output of the reference generator 1;

- a shaper of variable amplitudes of 5 pseudo-half-wave and phase signals 8 (Fig. 3) is intended for absolutely coherent generation of quasi-analog, for example, a sinusoidal signal of the action of Us from pulse pulses distributed along the PDF directions and changing as the amplitude values of each half-wave the generated signal Us, and its initial phase is proportional to the decimal weight 5 of the control code NB, which enters the memory register 16 via the control input 13, while the PDF of the P2-bit groups of outputs of the register and 16 are connected separately to the second control inputs of the logical keys 17, the outputs of which are connected to

multi-bit resistor dividers of the type R-2R or compensation, the outputs of which are connected to the inputs of the adder 19, the output of which is connected to the signal input of the sensor 3;

- a switch 9 is designed to bypass the sensor 3 when measuring and monitoring the insertion loss.

The operation of the device during phase detection of two unknown signals U4 (switch 9 is open) and Us (switch 9 is closed to point a) allows, after integration and analog-to-digital conversion, to measure and control the transmission coefficient (active part of the complex parameter of the phase sensor 3) in the form:

u ,, l | u; r yi .. ,, h (() (.) r

 K wa Kn PwiiU ..

the potential difference of the r-rG junction of the zener diode 28;

R is the resistance of the resistor 29;

RO is the resistance of the magnetoresistor RM at the voltage L0;

C is the capacitance of the capacitor 32;

n is the total resulting number of measurements.

The introduced phase shift is parametrically a reactive part of the complex parameter of device 3.

When the phase detection device with the switch 9 (Fig. 1) is closed to point a, the phase shift introduced by the controlled device 3 is compensated by the amount of phase compensation not only by the reference signals U2 and Uz, as in the prototype and analogue, but in contrast to them , and according to the quasi-analogue signal of the action of Us with the help of a distributor 7 and a shaper 8, and is determined in this case as

2 JC where Ф on (Ј) tn-Ј - phase shifts,

1chop

carried out by means of a shaper 2 by reference quadrature signals U2 and from;

Vmi, 2 (Ј) Vmi, 2 / NB; changes in the half-wave amplitudes of the quasi-analogue sinusoidal signal, which, in contrast to the prototype, are carried out with the aid of a distributor 7 and a shaper 8 of variable amplitude half-wave and phase signals;

p (Ax) - introduced by the controlled device 3 phase shift on the example of specific schemes of phase sensors, 45 defined as

p arctg

1

 CoYVp-n and p arctg 2 jrfe C RM (H)

respectively, where Vp-n is the controlled direct current voltage; From the initial capacitance of the pn junction of the zener diode 28 at k is the design coefficient characterizing the contact

h (

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f lLNon N00 J

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0

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0

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Non is the number of phase shifts and measurements from the reference signals selected by the required accuracy, which determines the magnitude of the phase shift 360 / N0n discrete set at the control input 12 (Fig. 1);

NB Non / Ke-1 - the number of required phase shifts of the quasi-analog exposure signal, providing the necessary increase in the speed of phase detection and measurement in Kb 2.3,., (Non + 1) times, which can be selected from the specified series of values of the speed coefficient Kb and which is set at the control input 13 (Fig. 1).

Amplitude-half-wave balancing of the areas of half-waves during phase detection and phase compensation by a quasi-analog signal can be carried out both separately and at the same time, mutually complementing each other in their advantages, providing an increase in the speed of phase detection by two or more times, while allowing to reduce the discretization of phase of shifts in the reference signal 360 / Non by an increase in the number N0n, which leads to an increase in accuracy at the chosen speed (increase in Kb), the fact that usually ( the prototype and analogue) with increased accuracy (increase in the number n0n) a decrease in the phase increment should snizhats performance hyperbolically in the accuracy of the coordinates - speed. At the same time, the dynamic stability of the operation of the device to accidental emissions is increased in terms of the measured parameters of the phase sensor 3.

Thus, a device that implements and discloses a phase detection method without decreasing the accuracy of measurements and monitoring or increasing it by decreasing the phase discreteness of the shaper 2, improves the speed due to the possibility of changing the half-wave amplitudes and the phase rotation of the quasi-analog sinusoidal signal by the shaper 8.

Moreover, the device fundamentally improves the accuracy of phase detection of measurement and control due to the fact that the proposed method provides as a deterministic connection of all spectrum parameters (frequency, phase, shape factor and level), i.e. full coherence and their independence over a wide range of changes, i.e. absolute coherence, which is interpreted by the n-dimensional vector, represented as the limiting compositional sum of the correlation coefficients of the parametric frequency functions and their subsequent derivatives with increasing order from member to member, while for absolute coherence the vector denotes one of the selected material points ball surface. Therefore, the proposed method improves the accuracy of phase detection by eliminating the error (e) inherent in the prototype and analogues when forming the quadrature of the reference signals, since it solves this problem by providing absolute coherence of the impact and reference signals, forming them quasi-analog all without exception and ensuring the determination of phase detection and thereby thereby determining the integrable voltage increment and its analog-to-digital conversion.

SUMMARY OF THE INVENTION A phase detection method by which an exposure signal and reference coherent signals is generated performs phase detection by multiplying a phase-shifted measured signal whose phase is changed proportionally to the measured parameter, with a reference signal and 90 ° phase-shifted

0 by a quadrature reference signal, the in-phase and quadrature parts of the measured signal are measured with respect to the corresponding reference signals, the phase shift of the reference signal is carried out, and

5 phases of the quadrature reference signal at an angle of 360 ° / N0n, where N0n is the number selected according to the required accuracy of measurements from the reference signal, characterized in that, in order to expand the field of application, increase the speed and accuracy of phase detection, the generated exposure signal is distributed over of time in the pdf directions and from the distributed signal of influence, an absolutely coherent quasi-analog sinusoidal signal with the number of quantization levels of the pcf is generated absolutely coherently, the amplitude is changed in the direction of decreasing if the first half-wave Umi is a quasi-0 analog sinusoidal signal, if the phase of the generated measured signal is shifted to the backward lag relative to the phase of the reference signal and / or to the direction of increasing the magnitude of the amplitude of the second half-wave of the second signal, and if the phase of the generated quasi-analog sinusoidal signal is shifted to the side leading relative to the phase of the reference signal, a change is made in the direction of increasing the amplitude of the first half-wave of the quasi-analog sinusoidal signal and / or in the direction of decreasing changes in the amplitude of the second half-wave Um2 of this signal, respectively, by the value of Umi / Ne and Um2 NB, where NB is the number of necessary changes in the amplitude of the corresponding half-wave Umi, Um2, and then at any of the indicated changes in one of the amplitudes of the half-waves

0, they carry out operations similar to those described above to form completely coherent, shifted by different values of fixed phases, several support quasicontinuous vertices

5 signals, then phase shifts of these signals are carried out by changing the beginning of the distribution of the exposure signal and the generated measured signal without destroying the coherence, regardless of their frequency, until a measurement is performed, corresponding to the procedure r o n a n n o g to zero value of voltage - signal.

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