RU1790031C - Device for recognition of radio signals - Google Patents

Abstract

The invention relates to radio engineering and can be used to recognize radio signals. The purpose of the invention is to increase the noise immunity and reliability of signals by suppressing spurious signals (interference) received via additional channels. The device comprises a frequency detector 1, spectrum analyzers 2, 6, 8, and 13, a frequency multiplier 3 by two, amplitude detectors 4 and 37, analog code converters 5, 10 and 14, comparison blocks 7 and 11, clipping block 9, detector 12 sign, elements And 15 and 16, logical processing unit 17, null-organ 18. Reference voltage generator 19, switches 20 and 28, amplifiers 21 and 23, phase shifters 22, 41 and 44 by 90 °, electron beam indicator 24, local oscillator 25, mixers 26, 35 and 42, amplifiers 27, 36 and 43 of intermediate frequency, a frequency multiplier 28 by eight, a frequency divider 29 by eight, a bandpass filter 30, phase detectors 31 and 39, a control element 32 and a recording unit 40. 4 ill. (L C

Description

h o o o so

The proposed device relates to radio engineering and can be used in devices for the detection and automatic recognition of amplitude-modulated (AM), frequency-modulated (FM) and phase-modulated (FM) radio signals with voice and telegraph messages, as well as broadband signals with linear frequency modulation (LFM) and multiple phase manipulation

(PSK). . ;; ; .

Known devices for the recognition of radio signals1:

Of the known devices, the closest to the proposed device is a device for recognizing radio signals, which is selected as a prototype.

However, the known device has low noise immunity and reliability of recognition of radio signals. This is explained by the fact that the same value of the intermediate frequency fnp can be obtained by receiving radio signals at two frequencies fc and fa, i.e.

fnp fc fr and fnp fr - fa.

Consequently, if the tuning frequency fc is taken as the main reception channel, then along with it there will be a mirror receiving channel, the frequency f3 of which differs from the frequency fc by 2 m and is located symmetrically (mirror) with respect to the frequency fr of the local oscillator. Conversion by the mirror channel of reception occurs with the same coefficient of conversion of CPR as by the main channel of reception. Therefore, it most significantly affects the selectivity and noise immunity of the device.

In addition to the mirror, there are other additional (combination) reception channels, the frequency of which can be determined from the following equality:

SL,. 1 g fK | - fr ± -fnp.

where m, n are integers.

The most harmful Raman reception channels are those generated by the interaction of the carrier frequency of the received signal with the second harmonic of the local oscillator frequency, since the sensitivity of these channels is close to the sensitivity of the main reception channel. So, the following parts correspond to two combinational reception channels:

fK1 2fr - fnp AND Тk2 2fr + fnp ,.

0

5

0

5

0

5

0

5

0

5

where 2fr is the second harmonic of the local oscillator frequency ...-.

The presence of false signals (interference) received via mirror and Raman channels leads to a decrease in noise immunity and reliability of recognition of radio signals.

In addition, the known device does not provide the ability to direction finding a radiation source of radio signals.

The aim of the invention is to increase the noise immunity and reliability of signal recognition by suppressing spurious signals (interference) received via additional channels.

This goal is achieved by the fact that the second and third mixers, the second and third intermediate frequency amplifiers, the second amplitude detector, the second phase detector, the registration unit, the second key, the adder, the second and third phase shifters and the first and second antennas, the inputs of which are are the same inputs of the device, the output of the first antenna is connected to the second input of the first mixer and the first input of the third mixer, the output of the second antenna is connected to the first input of the second mixer, the output of which is through the second an intermediate frequency amplifier is connected to the input of the second amplitude detector and the first input of the second phase detector, the output of which is connected to the input of the registration unit, the output of the second amplitude detector is connected to the first input of the second key, the second input of which is combined with the second input of the second mixer and connected to the output of the first amplifier intermediate frequency, the output of the second key is connected to the first input of the adder, the output of which is connected to the input of the frequency multiplier by eight, the second input of the second phase detector and the input of the second phase shifter is connected to the local oscillator output, the output of the second phase shifter is connected to the second input of the third mixer, the output of which is connected through a third intermediate frequency amplifier and the third phase shifter to the second input of the adder, the control electrode of the electron beam indicator is connected to the output of the frequency detector .

In FIG. 1 shows a structural diagram of the proposed device; in FIG. 2 is a frequency diagram explaining the process of forming additional reception channels; in FIG. 3 - time diagrams explaining the operation of the device; in FIG. 4 is a view of possible waveforms.

A device for recognizing radio signals comprises a frequency detector 1, a first instant spectrum analyzer 2, a two frequency multiplier 3, a first amplitude detector 4, a first analog code converter 5, a second instant spectrum analyzer 6, a first comparison unit 7, and a third instant analyzer 8 spectrum, clipping block 9, second analog-to-code converter 10, second comparison block 11, sign detector 12, fourth instant spectrum analyzer 13, third analog-to-code converter 14, first AND element 15, second AND element 16, block 1 7 logical processing, null-organ 18, the reference voltage generator 19, the first key 20, the first vertical amplifier 21, the first 90 ° phase shifter 22, the second horizontal amplifier 23, the cathode-ray indicator 24, the frequency converter 25, consisting of a first mixer 26, a first intermediate frequency amplifier 27 and a local oscillator 28, a frequency divider 29 by eight, a narrow-band filter 30, a first phase detector 31. a control element 32, a frequency multiplier 33 by eight, a first antenna 34 a second antenna 342, a second mixer 35, a second intermediate frequency amplifier 36, a second amplitude detector 37, a second key 38; a second phase detector 39, a recording unit 40, a second phase shifter 41 by 90 °. the third mixer 42, the third intermediate frequency amplifier 43, the third phase shifter 44 by 90 ° and the adder 45. Moreover, the mixer 26 is connected in series to the output of the local oscillator 28, the second input of which is connected to the output of the antenna 34, the intermediate frequency amplifier 2.7, mixer 35, the second the input of which is connected to the output of the antenna 342, an intermediate frequency amplifier 36, an amplitude detector 37, a key 38, the second input of which is connected to the output of an intermediate frequency amplifier 27, an adder 45, a frequency detector 1, an instant spectrum analyzer 6, block 11of equalities, an analog-code converter 14 and a logical processing unit 17, the second input of which is connected through an analog-code converter 5 to the output of the frequency detector 1, and the third input, through the analog-code converter 10, is connected to the output of the amplitude detector 4. K the output of the adder 45 is connected in series with a frequency multiplier 3 by two, an instant spectrum analyzer 8, a comparison unit 7, the second input of which is connected through the instant spectrum analyzer 2 to the output of the adder 45, a sign detector 12, and AND element 15. To the second output of the detector

12 characters in series element And 16. The second inputs of the elements And 15 and 16 are connected to the output of the converter 5 analog code. An amplitude detector 4, a clipping unit 9, and an instant spectrum analyzer 13, the output of which is connected to the second input of the comparison unit 11, are connected in series to the output of adder 45. To the output of the reference voltage generator 19, a key 20 is connected in series, the second input of which is connected via the organ-18 to the output of the comparison unit 7, a phase shifter 22 by 90 °, an amplifier 23, and a horizontal electrode of an electron beam indicator 24. A vertical electrode of which is connected through an amplifier 21 with the output of the key 20, and the control electrode is connected to the output of the frequency detector 1. A frequency multiplier 33 by eight, a frequency divider 29 by eight, a narrow-band filter 30, the second input of which are connected to the output of the adder 45 It is connected to the output of the key 20 and a control element 32. The output of which is connected to the input of the local oscillator 28. A phase detector 39 is connected in series to the output of the intermediate frequency amplifier 36, the second input of which is connected to the output of the local oscillator 28, and a recording unit 40.

The suppression of false signals (interference) received via the mirror channel at the frequency fs is based on the use of the phase compensation method

Suppression of false signals (interference) received via Raman channels at frequencies fVi and fK2. based on sequential double conversion of the carrier frequency of the received signal.

The phase shift A p, which determines the direction of the signal source to the radiation source, is measured by the phase method ... . . .-: ..- ..

A device for recognizing radio signals operates as follows.

Received signals, for example, with multiple phase shift keying (PSK)

Ui (t) Vc-cos 2jrfct + pk (t) + pi .. U2 (t) Vc fct + y (t) + F, 0 f Tc,

where Vc, fc, Tc, p, pz - amplitude, carrier frequency, duration and initial phases of signals ;.

pk (g) is the manipulated component of the phase that displays the law of phase manipulation in accordance with the modulating code M (t) (Fig. 3a), and pk (g) const for

K rh t (K + 1) rn and can change stepwise at t KGn, i.e. at the borders between elementary premises (K - 1, 2, ..;,: M-1);

Tn, N - duration and quantity of element; from which sigyals of duration Tc (Tc N gp) are present; with. the outputs of the antennas 34i and 34 are fed to the first inputs of the mixers 26, 35. and 42. The voltage from the outputs of the local oscillator 28 and the phase shifter 41 to 90 are supplied to the second inputs of the mixers 26 and 42; :;.:: ...- ,, .--.

..; tJri (t) VrС05 (2тг1 + рг),:.; ..:; Ur2 (t) Vr.COS (+ + .90 °), ;; X;:;

where Vr, fr, fr are the amplitude of the frequency and the initial phase; and the voltage of the local oscillator,., ..... The tuning frequency fHi and the bandwidth Afi of the intermediate frequency amplifiers 27 and 43 are selected as follows:

...:,.,: .. f.Hi fnp, Af i 2fnp. : ..

The tuning frequency fH2 and the passband Af of the intermediate frequency amplifier 36 are selected as follows;

. fH2 fr, Dt2 2fnp. , ..: .....;., -: In mixers 26 and 42, the received fMn signal is converted to the voltages of the following frequencies :; ... . fd fc-fr frip,.:. ; -. ; V -. . : .., fc2-; 2fr - fc,;.;;;; /: ;;. where the first index denotes the channel by which pd My receives the signal; the second index denotes the harmonic number of the heterodyne frequency a involved in the conversion of the carrier frequency of the received signal;

However, in the passband Afi of the amplifiers 27 and 43 of the intermediate frequency of the pop - ..,. Give voltage with a frequency fci,

(p + pnp {,

Unp2 (t) + Vnp Лfпpt + рк ($ + - 90 °, - {.:.;; ;;;;:; V0 t tc,, ..

where Vnp .KiVcVr, - -j -; y; ...

Ki conversion ratio | Mixers; flip fс - fr - intermediate frequency;

 ; . f. , ..,., ....,.:. :.

The voltage Unpiftj from the output of the intermediate frequency amplifier 27 is supplied to the second input of the mixer 35, at the output of which the voltage is formed:

Unp3 (t} Vnpi -so5 (+ pg + D0, 0 t TS,

where Vnpi 2 KiVc Vnp ,. . -. ;

Ay pi (f is the phase shift that determines the direction of the PSK signals to the radiation source. .- ...:

An amperage voltage is allocated to the amplifier at 36 intermediate frequencies. It is detected by amplitude detector 37 and received: ID control input of key 38.

opening it, Keys .20 and 38 in the initial state are always closed. In this case, the voltage. Unp (t) from the output of the amplifier 27 intermediate frequencies through the public key 38 At the same time: rtoeT y rfaet to the first input

adder, 45.- ::,; .-- v - ;; ... -. ::. ,. ; The voltage Unp2 (t) from the output of the intermediate frequency amplifier 43 is supplied to the input of the phase shifter 44 by 90 °, at the output of which the voltage is generated.

.Vv / v,. /. ,,.; : D;: ..., - /,; -; ::

Unp4 (t) Vnp - COSpTT fnpt i pk (1} +

+ 95pr1 - 90 ° + 90 ° Vnp-cos 2 rfnpt. +

 ::. - .. V), 0. : This voltage is applied to the second input of the adder 45, at the output of which a total voltage is generated.

U2 (t) V2- cost2 jrfnpt + VKW + Pi

.-. ..; ,:.:,

where VS 2VnP /. ;;. ::,;.:. :. . ; This voltage is simultaneously applied to the inputs of frequency detector 1, spectrum analyzer 2, frequency multiplier 3 by two, amplitude detector 4 and frequency multiplier 33 by eight. ; ; ;; ;.:;

Using the spectrum analyzer 2, the spectrum width Afc of the received signal is measured, which is at least equal to the duration

elementary parcels tl (Lts)

;. . . . . . . -; / ..: -; ..:. . .. P

If the input device. Receives a signal with a two-phase: manipulation

    ; .yj-: -......

DfMn, p (t) 0, -n, I, 4 l; then the output

a frequency multiplier of 3 by two is formed

signalN with a single phase manipulation tsoyosos &Mn; (t) 0, lg, 2l:, 3l :, width

spectrum Af2 of which is also determined

duration gp elementary premises

(Af2 r-) and measured by analyzer 8

   :

 spectrum. ;. : - / .:: /: -:: /; .-

If a signal with three-fold phase manipulation of the TFMn arrives at the device input,

(t) 0, f, f jt, n,:, ljil then at the output of the frequency multiplier 3 by two, a DPSK signal is generated to (g) 0, -k-, 7G,

35 7 y p, 2 l, - g p, 3 p, -j l.

Therefore, if a signal with multiple phase shift keying is input to the device, then the inputs of the comparison unit 7 receive the same values of the spectrum width of the received signal at the fundamental Afc and doubled Af2 frequencies (Afc Af2) ...-.-. :

The indicated equality fixes the zero-organ 18, issuing a signal that opens the key. 20. The voltage of the reference voltage generator 19 through the open switch 20 through the vertical amplifier 2.1 is supplied to the vertical electrode of the cathode ray indicator 24, and through the phase shifter 22 to 90 ° and the horizontal amplifier 23 to the horizontal electrode of the indicator 24, form its screen is a circular scan. At the same time, the voltage of the reference voltage generator 19 is supplied through the open switch 20 to the first input of the phase detector 31.

The voltage U2 (t) from the output of the adder 45 simultaneously enters the input of the frequency multiplier 33 by eight, at the output of which a harmonic oscillation is generated,

Uz (1) VЈ cos (16 rffnpt + 8 phpi). 0 t TC.

So, as 8 pK (t) 0, 4tg, 8l; 12 in the case of receiving the DPSK signal and 8 y (t) 0.2 lg, 4tg, btg, 8 l :, Yul; 12l; 14l in case of receiving the TPSK signal, then there is no phase manipulation in the indicated oscillation. The spectral width Afs of the harmonic oscillation is determined by the duration Tc of the signal a (Afe т), i.e.

 /. . I s

the width of the spectrum Afs of the harmonic vibration became N times smaller than the width of the spectrum

Afc of the input PSK signal (ugg N).

Therefore, when the frequency is multiplied by eight, the spectrum of the input PSK signal is convolved.

. The harmonic oscillation Us (t) is supplied to the input of the frequency divider 29 by eight, the output of which is formed

140 VZ -C0s (27rfnpt + pnpl), 0 t TS,

which is extracted by a narrow-band filter 30 and fed to the second input of the phase detector 31. If, under the influence of various destabilizing factors, the intermediate frequency fnp is not equal to the frequency fo of the reference voltage generator 19 (fnp fo), then the voltages supplied to two the inputs of the phase detector 31 differ in phase. In this case, the output

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5

0

5

0

5

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5

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5

a phase detector 31 generates a control voltage whose amplitude and polarity depend on the degree and direction of the deviation of the intermediate frequency fnp from the frequency fo of the oscillator. 19 of the reference voltage. The control voltage through the control element 32 acts on the local oscillator 28, changing its frequency fr so that the equality fnp fo is maintained. In this case, a stable circular scan is formed on the screen of the indicator 24. .

The voltage US (t) (Fig. 36) from the output of the adder 45 is simultaneously fed to the input of the frequency detector 1, the outputs of which form a sequence of short-wave multipolar pulses (Fig. Sv). the temporary position of which corresponds to the moments of the abrupt change in the phase of the received signal. UZ (r) (Fig. 36). The indicated sequence of pulses from the output of the frequency detector 1 is supplied to the control electrode of the indicator 24 and modulates its electron beam in brightness; A stable image is formed on the screen of the indicator 24 in the form of several bright points located on a circle (Fig; 4). The number of points corresponds to the multiplicity of phase manipulation m, and the angular distance between them is equal to the value of the phase jumps of the received PSK signal. Using a stable oscillogram on the screen of the indicator 24, it is possible to visually assess the multiplicity m of phase manipulation and the value of jumps. The phases of the received PSK signal and, therefore, make its reliable recognition. In case of frequency inequality (fnp fo), the brightness marks will move around the circle with the difference frequency and reliable recognition of signals with multiple phase manipulation is not possible. .

The voltage Unp3 (t) from the output of the intermediate frequency amplifier 36 is supplied to the first input of the phase detector 39, the second input of which is supplied with the voltage Uri (t) from the output of the local oscillator 28. A low-frequency voltage is generated at the output of the phase detector 39. Un ()) VH-COS Ap,

where VH 2-K2VnPrVr,

“2 - transfer coefficient of the phase detector;

& q -ipi- (p - 2 tt-% COS y,

d — measuring base (distance between antennas);

A - wavelength ;,. . y-angle of arrival of radio waves. This voltage is detected by the registration unit 40. -. .

When a signal with a frequency modulation (FM) arrives at the input of the device, the output voltage of the frequency detector 1 is allocated, which is applied to one of the inputs of the instant analyzer 6, through the clipping unit 9, to the analyzer 13 instant spectrum and through the converter 5 analog code to one of the inputs, block 17 of the logical processing. The responses generated at the outputs of analyzers b and 13 are fed to the corresponding inputs of the comparison unit 11, i.e., at the output of which, if a signal with frequency modulation (FM) is applied to the input of the device, the voltage appears, and in the case of a signal with frequency manipulation (FMN) voltage is absent. Therefore, at the output of the converter 14, an analog code is generated in the first case, one, and zero in the second. From the output of the converter 14, the normalized voltage enters the block 171 at the corresponding output of which a unit voltage occurs. . The recognition of amplitude-modulated (AM) and amplitude-manipulated (AMn) signals occurs in a similar way.

For recognition of linear frequency modulation (LFM) signals and single-phase manipulation of the OFMn, PX. (, Tg), the device compares the width of the amplitude spectra of the received signal at the fundamental and doubled frequencies. In this case, that the spectrum width of a signal with a linear frequency modulation at twice the frequency is two times larger than the width of its spectrum at the fundamental frequency, and the spectrum of a signal with a single phase manipulation at twice the frequency is N times narrower than the spectrum of the same signal on the fundamental The width of the amplitude spectrum of the received signal is determined using analyzer 2 and after doubling its frequency in the multiplier 3 using analyzer 8. As a result of the comparison of the obtained spectral widths, the output of the comparison unit 7 generates a voltage of a certain polarity which is supplied to the input of the sign detector 12. If the recognized signal has a linear frequency modulation, then the output of the comparison unit 7 forms a negative voltage, which is transmitted through the corresponding output of the detector 12 at the first input of AND element 15, at the second input

which receives a single signal from the output of the Converter 5 analog code. Therefore, with linear frequency modulation, a unit voltage is generated at the output of AND element 15, and there are no signals at the output of block 17.

If a signal with a single phase shift is fed to the input of the device, then the output of the comparison unit 7 generates a positive voltage, which passes through the sign detector 12 to the first input of the And 16 element, to the second input of which a signal from the output of the analog-to-converter 5 is supplied. Consequently, during a single phase manipulation of the received signal, a unit voltage is formed only at the output of the And 16. element. The operation described above corresponds to the case of receiving signals on the main channel at a frequency fc.

If false signals (interference)

Uni (t) ynrcos (2jrf3t + pni),.

Un2 (t) Vn2 COS (2 + pn2),

where Vni, Vn2, fp, fwi are the amplitudes and initial phases of interference;

If they are received through the mirror channel at a frequency of m3, then in mixers 26 and 42 they are converted to voltages of the following frequencies:

fs1 fr - fa Tpr,. -. f32 2fr-f3.

However, only the voltage with the frequency mk1 falls into the passband Afi of the amplifiers 27 and 43 of the intermediate frequency

Unp5 (t) Vnp2 -COS (27r fnpt + ppr2), Unp6 (t) Vnp2 COS (2 TTfnpt + pnp2 + 90 °),

rfleVnp2 KiVnrVr,

fnp fr - fз - intermediate frequency;

rpr2.

The voltage Unps (t) from the output of the intermediate frequency amplifier 27 is supplied to the second input of the mixer 35, at the output of which a voltage is generated

Unp7 (t) Vnp3 COS (2 JTfrt + pr + A pl),

where Vnp3 Vn2 -Vnp2,

 ..

The indicated voltage is extracted by the intermediate frequency amplifier 36, detected by the amplitude detector 37, and arrives at the control input of the key 38, opening it. In this case, the voltage Unp5 (t) from the output of the intermediate frequency amplifier 27 through the public key 38 is supplied to the first input of the adder 45.

The voltage Unp6 (t) from the output of the intermediate frequency amplifier 43 is supplied to the input of the phase shifter 44 by 90 °, at the output of which a voltage is generated

UnP8 (t) Vnp2 COS (2jr fnpt + / 5pr2 + 90 ° + + 90 °) -Vnp2 COS (2 Jlfnpt + (pnpll

This voltage is applied to the second input of the adder 45. The voltages Unp5 (t) and Unps (t) supplied to the two inputs of the adder 45 are compensated at its output. Consequently, spurious signals (interference) received on the mirror channel at the frequency fa are suppressed. :; . If false signals (interference) are received on the first combinational channel at a frequency fKi, then in mixers 26 and 42 they are converted to voltages of the following frequencies:

 fn fKi - fr,

.. .-; - ;. fi2 2fr- fKi fnp. However, only the voltage with frequency fi2 falls into the passband Afi of the amplifiers 27 and 43 of the intermediate frequency

Unp9 (t) Vnp2 COS (2 + 90pr2), Unpio (t) Vnp2 -С05 (2ЛГ fnpt + Ipnpz + 90 °),

where fnp 2f.-r - fxi is the intermediate frequency.

The voltage Unp9 (t) from the output of the intermediate frequency amplifier 27 is supplied to the second input of the mixer 35, at the output of which a voltage is generated. .,...../ 1

. UnPn (t) Vnp3; cos (4jrfrt + fr).

This voltage does not fall into the passband Afa of the intermediate frequency amplifier 36, the key 38 does not open and the false signals (interference) received on the first combinational channel at a frequency fKi are suppressed.

For a similar reason, they are suppressed and

false signals (interference) received on the second Raman channel at frequency fo. . ... Thus, the proposed device in comparison with the prototype provides increased noise immunity and reliability p aspect recognition of signals. This is achieved by suppressing false signals (interference) received by additional (mirror and Raman)

channels. In addition, the device according to the invention allows the measurement of the phase shift A.ip, which determines the direction of the signal source. Thus, the functional capabilities of the device

expanded.

SUMMARY OF THE INVENTION A device for recognizing radio signals, comprising a frequency multiplier of eight, a frequency divider of eight, a narrow-band filter, the output of which is connected to the first input of the first phase detector, the output of which is connected through a series. a first control element and a local oscillator connected to a first input of a first mixer; the output of which is connected to the input of the first intermediate frequency amplifier, the input of the frequency multiplier by eight is combined with the inputs of the first amplitude detector, the first frequency detector, the first instant spectrum analyzer and the frequency multiplier by two, the output of which is connected through the second instant spectrum analyzer to the first input of the first comparison unit the output of which is connected directly to the input of the sign detector and, through the zero-organ, to the first input of the first key, the second input of which is connected to the output of the op voltage

5 ..: ...

the output of the first key is connected directly to the second input of the first phase detector, through the first amplifier - with the vertical electrode of the electron beam indicator and through series-connected the first phase shifter and second amplifier - with the horizontal electrode of the electron beam indicator, the output of the first instant spectrum analyzer connected to the second input of the first comparison unit, the output of the first frequency

 The detector is connected via the first analog-code converter to the first inputs of the logical processing unit and the first and second elements AND and directly, to the first input of the clipping unit and the first input of the third instant spectrum analyzer, the output of which is connected to the first J-input of the second comparison unit, the output an amplitude detector is connected via a second analog-to-code-s converter. the second input of the logical processing unit and, indirectly, with the second input of the third instant spectrum analyzer and the second

0

the input of the clipping unit, the output of which through the fourth analyzer of the instant spectrum is connected to the second input of the second comparison unit, the output of which through the third converter is an analog-code connected to the third input of the logic processing unit, the outputs of which are the first outputs of the device, the first and second outputs of the detector signs are connected to the second inputs of the first and second elements And, respectively, the outputs of which are respectively the second and third outputs of the device, characterized in that, in order to increase In terms of reliability and reliability of the device, the second and third mixers, the second and third intermediate frequency amplifiers, the second amplitude detector, the second phase detector, the registration unit, the second key, the adder, the second and third phase shifters, and the first and second antennas, whose inputs are the inputs of the same device, the output of the first antenna is connected to the second input of the first mixer and the first input of the third mixer, the output

the second antenna is connected to the first input of the second mixer, the output of which through the second intermediate frequency amplifier is connected to the input of the second amplitude detector and the first input of the second phase detector, the output of which is connected to the input of the registration unit, the output of the second amplitude detector is connected to the first input of the second key, the second the input of which is combined with the second input of the second mixer and connected to the output of the first intermediate frequency amplifier, the output of the second key is connected to the first input of the adder, the output of which connected to the input of the frequency multiplier by eight, the second input of the second phase detector and the input of the second phase shifter are connected to the local oscillator output, the output of the second phase shifter is connected to the second input of the third mixer, the output of which is connected through a third intermediate frequency amplifier and the third phase shifter to the second input the adder, the control electrode of the electron beam indicator is connected to the output of the frequency detector.

 2jr / A

J;

etc

h / j zg fa

.-S b

At

-aЈ - 9-

Yes %

No.

0/211