KR20090105773A - Measurement Device of Internal Impedance or it's effective value, And Method Thereof - Google Patents

Abstract

PURPOSE: A measurement device of internal impedance or its effective value, and a method thereof are provided to flow sinusoidal wave measurement current signal. CONSTITUTION: A measurement device of internal impedance or its effective value, and a method thereof calculates the internal impedance or its effective value of the measured object. A step that controls a measuring signal of a ripple current wave discharge current having sinusoidal wave shape flows the measured object. The internal impedance voltage signal of the measured object generated by the measurement current signal of the sinusoidal wave ripple current is obtained. The internal impedance or the effective value is calculated by the constant current signal and the internal impedance voltage signal.

Description

Measurement device of internal impedance or its effective component and method thereof {Measurement Device of Internal Impedance or it's effective value, And Method Thereof}

The present invention relates to a device and a method for measuring the internal impedance of an object to be measured or an effective component thereof, and more particularly, to generate a pulse wave-shaped discharge current including a sinusoidal current which is relatively easy to generate as a measurement current signal. The present invention relates to a measurement computing device and a method for calculating an element corresponding to an internal impedance of an object to be measured or an effective component thereof (or loss angle) by flowing in water and measuring an internal impedance voltage signal corresponding thereto.

In general, the internal impedance or conductance value is measured in order to diagnose the deterioration degree of each cell constituting the industrial storage battery system, and the measurement technique thereof is an AC current injection method or an instant load discharge method ( Momentary Load Test DC Measurement), DC method for measuring internal resistance through the correlation between the battery's normal phase voltage drop and the load current during discharge, and the voltage and current of the battery under pulse discharge. Cadex Ohm Test, which measures the internal resistance through correlation. Since the internal impedance or conductance values measured by the above methods are different from each other in their measuring method or measurement signal frequency, they may have mutual differences and have advantages and disadvantages.

In the case of DC method, the measurement method is relatively simple, so it is easy to implement the measurement circuit.However, it is necessary to discharge by using a very large current of 1.0 C ~ 4.0 C or more as the measurement current, so that the accuracy can be increased. During discharge, the discharge current flows from the charging device, which needs to be taken into account when measuring.

In addition, the internal circuit of the battery can be equalized by a combination of RLC equivalent circuit elements, and the internal impedance value can be expressed as Z = R + jX, the magnitude of which is calculated by taking the square root of R ² + X ² , where the internal impedance is effective. The component is represented by a value corresponding to the R component. Also, the admittance, which is the inverse of the internal impedance value, is expressed as Y = G + jB, where G is expressed as conductance and uses Siemens units.

For a long time, the internal impedance measurement method by AC current injection method has been generally adopted. The AC current injection method inputs a sinusoidal alternating current (I _S ) as a measurement current signal to both ends of a terminal to be measured such as a battery and corresponds to an internal impedance value. The internal impedance value is measured and calculated by measuring the resulting voltage drop component (hereinafter referred to as internal impedance voltage V _IS ).

The AC current injection method will be described in detail. When a sinusoidal AC current I _S is generated from a constant current source or a voltage source having a large internal impedance, and is input to both terminals of the EUT through an AC 4-terminal network, the terminal of the EUT is measured. In response to the sinusoidal AC current I _S , a sinusoidal internal impedance voltage V _IS signal is measured. The internal impedance voltage (V _IS ) signal is converted and amplified into a pure AC signal through an operational amplifier coupled as a capacitor, and the sinusoidal AC current (I _S ) signal is converted into a voltage signal through current sensing means (classifier or DC converter). After conversion and amplification by the operational amplifier, the two values are input to a digital computation circuit (embedded circuit) composed of an A / D converter and a CPU.

의 수식원리에 따라 연산되어 진다. 여기서, V_{IS , RMS}는 임피던스 전압(V_IS)의 실효치이고 I_{S, RMS}는 정현파 교류전류(I_S)의 실효치이며, θ 는 임피던스전압(V_IS)과 정현파 교류전류(I_S)의 상호간 위상차 각이다.The predetermined arithmetic program mounted on the digital arithmetic circuit is performed and the internal impedance effective value is

It is calculated according to the mathematical principle of. Where V _{IS , RMS} are the effective values of the impedance voltage (V _IS ), I _{S, RMS} are the effective values of the sinusoidal AC current (I _S ), and θ is the mutual value between the impedance voltage (V _IS ) and the sinusoidal AC current (I _S ). Phase difference angle.

As described above, the AC current injection method has been widely used, and since a measurement operation circuit or a calculation algorithm has been developed for this, the internal impedance and its effective component can be obtained using a proven measurement circuit or calculation algorithm. It has the advantage of being able to measure accurately.

1. YUASA Technical Report; No.72, April 1992.

2. Korean Patents; Patent Application No. 10-2006-0088525, filed on September 13, 2006, the device for measuring the internal impedance effective component of the storage battery and its method.

3. PCT Patent; PCT / KR2006 / 004845, WO / 2007/066911

Apparatus for measuring the internal impedance effective ingredient of a battery, which is filed on September 13, 2006, and published on June 13, 2007, by the inventor of the present invention, or a Korean Patent Application No. 10-2006-0088525 or PCT Patent PCT / KR2006 / 004845. And in the method, as described above, when adopting a conventionally used AC current injection method, there is a difficulty to generate a large sinusoidal AC current Is, a sine wave as a means for overcoming this Hardware filtering means or built-in filtering for injecting PWM measurement signal with basic measurement frequency into discharged object or discharging with PWM current, without using AC current (Is) By performing the program to obtain the measured current signal and the impedance voltage signal of the sine wave component, the internal impedance value of the fundamental measurement frequency or It suggests a method to measure and calculate its effective value.

In addition, in Korean Patent Nos. 10-2003 -0028521 and 10-2004 -0007050 filed by the present inventors, when calculating the internal impedance or its effective value using the above measurement calculation methods, The schemes include algorithms to eliminate the effects of high frequency ripple voltage.

When measuring a large capacity battery, the internal impedance value of the battery is very small in units of several milliohms (mΩ), while the sinusoidal AC current (I _S ) required for measurement has a limited size. The impedance voltage (V _IS ) signal of the battery cell measured at is below the level of several mV, which is much smaller than the harmonic ripple voltage caused by the charging current generated during charging, and the internal impedance measurement is influenced by the ripple voltage noise. You can easily get.

Therefore, in the AC current injection method, in order to reduce the influence of harmonic ripple voltage noise and increase the measurement accuracy, the internal impedance voltage (V _IS ) signal should be generated at a large value. Thus, the impedance voltage (V _IS ) signal is generated at a large value. In order to generate a large sine wave AC current (Is) of several amps or more, a sinusoidal current generation circuit having a relatively large capacity and a control power supply thereof are required, and the circuit configuration is complicated to implement. There was a problem that the manufacturing price is rising.

SUMMARY OF THE INVENTION The present invention has been made to solve the above problems, and does not have a complicated circuit for generating a sinusoidal alternating current as in the prior art, but has a sinusoidal shape having a predetermined frequency with respect to an object to be measured (for example, a battery column or a unit cell). By discharging so that an excitation pulse wave current flows, the measured current signal of a sine wave shape can flow to a to-be-tested object.

In addition, various wave filters such as low pass filter (LPF), high pass filter (HPF), or band pass filter for filtering the measurement current signal by using the sine wave measurement current signal instead of the square wave measurement current signal as the measurement signal. There is no need for a hardware-configured filter means such as, and also has the advantage that the execution of the filtering program is not required during the operation.

In addition, an internal impedance voltage signal generated corresponding to a sine wave-shaped measurement current signal can be obtained by using a measurement operation circuit and / or an algorithm similar to the AC current injection measurement method. It can be measured.

) 및 손실각 tanδ값)을 측정하는 연산방법은, 정현파 형상을 가진 맥류파 방전전류의 측정신호(정현파 맥류 형태의 측정전류신호)가 피측정물에 흐르도록 제어하는 단계; 상기 정현파 맥류 형태의 측정전류신호에 의해 발생되는 내부 임피던스 전압 신호를 구하는 단계; 및 상기 측정전류신호 및 내부 임피던스 전압신호 성분을 이용하여 내부 임피던스 또는 이의 유효치를 연산하는 단계;를 포함한다.To achieve the above object, the internal impedance of an object to be measured or an effective value thereof (or an ESR value of an internal resistance component) according to the present invention.

And a loss angle tan δ), the method comprising: controlling a measurement signal of a sine wave discharge current having a sine wave shape (a measurement current signal in the form of a sine wave pulse wave) to flow through the object to be measured; Obtaining an internal impedance voltage signal generated by the measured current signal in the form of the sinusoidal pulse wave; And calculating an internal impedance or an effective value thereof using the measured current signal and the internal impedance voltage signal component.

The pulsed wave discharge current measurement signal having the sinusoidal wave shape may be a pulse wave type waveform including a DC current generated by discharging a measurement target object such as a battery under measurement.

In addition, the sine wave-shaped pulse wave discharge current measuring current signal generation method is characterized in that the output voltage is linearly controlled using the active operation control region of the transistor.

In addition, the method for generating the measurement current signal of the sine wave discharge current of the sine wave shape may further include being controlled by the sine wave PWM switching method.

Further, in the present invention, the measurement current signal of the pulse wave discharge current may be synchronized with a clock pulse signal output from the MPU of the operation control circuit.

In addition, the present invention may be determined such that the frequency of the measured current signal is equal to any one selected from 0.5 times, 50 times (60 + 60) times the commercial power frequency, (n + 0.5) times, 5 Hz or an integer multiple thereof, or 10 Hz or an integer multiple thereof. It can be characterized by the presence.

The sinusoidal pulse wave discharge current generation method is characterized in that the voltage is linearly controlled using the output circuit side control means of a commercially available audio amp element.

Further, if an output current signal having a satisfactory size cannot be obtained as the output circuit side control means of the audio amp element, an output amplification means 34 can be further configured on the output side thereof to amplify the output current magnitude.

In addition, the pulse wave discharge circuit 2 of the present invention, A sine wave is generated by the sine wave generating means 31 by receiving the clock pulse 19 from the MPU of the embedded system 16, and controlling or amplifying the sine wave by the linear amplifying means 33, or PWM switching control means ( 44) has a function of generating a pulse wave discharge current to have a predetermined size by PWM control the output voltage.

) 및 손실각 tanδ값)를 연산하는 단계에서는, 충전시 발생되는 고주파 리플전압의 영향을 배제할 수 있도록 하기 위하여 이미 공지된 측정 연산 알고리즘을 그대로 적용할 수 있다.In addition, in the present invention, the internal impedance or its effective value (or the ESR value which is the internal resistivity)

) And the loss angle tan δ), a known measurement algorithm may be applied as is so as to exclude the influence of the high frequency ripple voltage generated during charging.

In order to exclude the influence of the harmonic charging current, the frequency of the greatest common divisor is obtained by mutually adding and subtracting all the frequency components forming the measured current signal or the AC voltage (V _SM ) or finding the greatest common divisor between the mutual addition and subtraction results. The method may include determining a constant integral period T _D necessary for the calculation as a period corresponding to or an integer multiple of the period.

In addition, selecting a frequency of the measured current signal; And / or calculating the calculation terms m1, m2, m3 and m4 from the AC voltage V _SM , the measured current signal, the cosine wave C1 and the sine wave S1, respectively; Add and subtract all frequency components forming an AC voltage (V _SM ) or a measured current signal mutually, or obtain a maximum common divisor between the result values obtained by mutually adding and subtracting all frequency components to be filtered and corresponding to the frequency of the maximum common divisor. Determining a constant integral period (T _D ) required for a calculation as a period or an integer multiple of the period; And calculating the calculation terms M1, M2, M3, and M4 composed of DC components only by integrating the calculation terms m1, m2, m3, and m4 during the predetermined integration period (T _D ). .

In addition, according to an embodiment of the present invention for achieving the above object, the internal impedance measurement and calculation device of the measurement object is a pulse wave containing a sinusoidal current in the calculation operation of the internal impedance of the measurement object or its effective value component A pulse wave discharge circuit 2 for generating a measurement current signal having a shape; Current sensing means (4) for detecting said pulsed wave shaped measurement current signal flowing through said object to be measured; And a measurement operation circuit (1) which calculates an internal impedance or an effective value thereof using the measurement current signal component and the component of the impedance voltage V _IS .

In addition, in the present invention, the measurement operation circuit (1) includes a differential amplifier circuit (10) for dividing or insulating amplifying the terminal voltage (Vp) of the object to be measured, such as the battery; A DC coupling circuit (11) for filtering only the impedance voltage (V _IS ) from the terminal voltage (Vp); Filter means (12) for filtering the impedance voltage and the similar frequency component of the frequency component necessary for the measurement from the impedance voltage (V _IS ); And An A / D converter 15 for converting the analog signal filtered from the filter means 12 into a digital signal; And an MPU and a peripheral circuit thereof for calculating an internal impedance through a built-in program.

The filter means 12 may generally implement the function by adopting only a filter circuit composed of hardware, but the present invention is not limited thereto, and the filter means 12 may simplify the hardware or perform a filtering program inside the measurement operation device to maximize the filtration effect. This can be done by subsidizing the function or by using only a filtering program.

In addition, Korean patent; The present invention can be used as another embodiment of the present invention by applying the technical idea of the present invention to an on-line measuring circuit known in Korean Patent Application No. 10-2006-6088525. That is, in real time, the measurement calculation device of the internal impedance of each battery cell or its effective value of the battery string including a plurality of batteries includes a pulse wave discharge circuit for flowing a pulse wave discharge current having a sinusoidal shape to each battery column or each cell (2). )Wow; The current sensing means 5a to 5n provided in the storage columns 31a to 31n or the current sensing means 4 provided to the output terminal of the discharge circuit 2, or the measurement current signal from the measurement current circuit 1 Switching means 20 for switching to; Current connection means (21) for switching the output current of the pulse wave discharge circuit to each of the battery rows (31a to 31n); And a measurement calculation circuit 1 for calculating an internal impedance or an effective value thereof by a known calculation algorithm using a component of the measurement current signal and an impedance voltage V _IS component.

The apparatus may further include current sensing means 5a to 5n for detecting an alternating current I _B including a measurement current signal flowing through each of the battery rows 31a to 31n.

The above objects, features, and advantages will become more apparent from the following detailed description taken in conjunction with the accompanying drawings, whereby those skilled in the art may easily implement the technical idea of the present invention. There will be.

As described above, the present invention has a disadvantage in that the circuit becomes complicated and the manufacturing price increases in implementing the current generating power supply circuit for generating the sinusoidal AC current Is, which is a measurement current signal, in the conventional method.

According to the present invention, it is possible to obtain a desirable measurement result by using a measurement operation algorithm similar to the AC current injection method, and does not require a voltage source or a current source for generating a sinusoidal current, thus eliminating the need for a control power supply of the sinusoidal wave generation circuit. This has the advantage of being simplified.

In addition, when a plurality of battery cells are measured online, a current sensing means such as a shunt or a direct current converter (DC.CT) may be used to convert a DC current waveform including a charge ripple generated during charging in a battery string (string). Through the pulse wave current in the sinusoidal shape to obtain the impedance voltage (V _IS ) signal generated by this, and through the calculation algorithm has the effect of accurately calculating the internal impedance or its effective value (resistance component) have.

In addition, the present invention can be designed so that the area occupied by the pulse wave discharge circuit (2) can be designed to reduce the external size of the internal impedance measurement and calculation device.

1 is a conceptual diagram of a method for measuring internal impedance by a pulse wave-shaped discharge current of the present invention.

2 is a configuration diagram of an internal impedance measurement method by a discharge current of a pulse wave shape as a representative embodiment of the present invention.

3 is a configuration diagram applied to an on-line measuring apparatus according to an embodiment of the present invention.

4 is an embodiment of a measurement operation circuit of the present invention.

5 is a pulse wave-shaped discharge current waveform and an output voltage waveform of the pulse wave discharge circuit in the present invention.

6 is a schematic diagram of a pulse wave-shaped discharge circuit as an embodiment of the present invention.

7 is another embodiment of the pulse wave discharge circuit according to the present invention.

8 is a circuit diagram of a pulse wave generating circuit using a PWM switching control method according to an embodiment of the present invention.

9 is a schematic diagram of another discharge circuit of a pulse wave shape which is an embodiment of the present invention.

10 is a pulse wave discharge circuit of a square wave clock pulse input type according to another embodiment of the present invention.

Fig. 11 is a control step of the sine wave discharge current in the sine wave shape in the present invention.

As shown in the Figure 1, the aneurysm when the wave discharge circuit is operated the discharge current (I _SD) that contains the sine-wave current to the battery cell of the measurement target pulsating wave-like flow, the terminal voltage (Vp) of the battery cells The impedance voltage (V _IS ) signal is generated with respect to the sine wave measurement current signal included in the pulse wave discharge current (I _SD ), and the impedance voltage (V _IS ) component is formed on the internal voltage (V _E ) at no load of the battery cell. Included in overlapping form.

At this time, the DC average current included in the pulse wave discharge current (I _SD ) does not contribute to generating the internal impedance voltage (V _IS ) signal, but results in lowering the charge internal voltage (V _E ) at no load of the battery cell. Since it is necessary to minimize the DC average current.

On the other hand, the internal impedance voltage (V _IS ) signal included in the form of superimposed on the charging internal voltage (V _E ), which is the terminal voltage (Vp) of the battery cell, the DC component is removed through the DC coupling circuit and the pure impedance of the sine wave shape It is desirable to obtain a voltage (V _{IS '} ) component and amplify it to a static magnitude before inputting it to the A / D converter.

In addition, if the magnitude of the sine wave measurement current signal in the pulse wave discharge current (I _SD ) is relatively large, it can be directly inputted to the A / D converter to calculate the magnitude of the pure sine wave measurement current signal in the calculation program execution step. If the sine wave measurement current signal is small in the pulse wave discharge current (I _SD ), after removing the DC component, only the pure sinusoidal AC component (I _{S '} ) is amplified to a static magnitude and inputted to the A / D converter. It is preferable.

× 10³ 의 수식원리에 따라, 상기 맥류파 방전전류(I_SD)의 측정전류신호 주파수에 해당되는 내부 임피던스 또는 유효성분 값이 연산될 수 있게 된다.The sinusoidal measurement current signal I _{S '} and the pure impedance voltage V _IS' signal included in the pulse wave discharge current I _SD obtained above are input to an A / D converter and converted into digital values. Based on the converted digital value, the operation program built in the CPU is executed and mΩ =

According to the mathematical principle of × 10 ³ , the internal impedance or the effective component value corresponding to the measurement current signal frequency of the pulse wave discharge current I _SD can be calculated.

Hereinafter, specific embodiments of the present invention will be described in detail. Figure 2 is a representative embodiment of the present invention, the basic configuration of the internal impedance measurement method by the discharge current of the pulse wave shape.

The current sensing means 4 is connected to the output side of the pulse wave discharge circuit 2, and when the pulse wave discharge circuit 2 is operated, the heat or unit cells of the battery to be measured are discharged to discharge the source terminal of the 4-terminal network. Through the pulsed wave discharge current (I _SD ) flows to the storage cell or the unit cell through the measurement, the magnitude of the pulse wave discharge current (I _SD ) is sensed by the current sensing means 4 and the sensing of the 4-terminal network The internal impedance voltage (V _IS ) signal is sensed through the terminal and the internal impedance or the effective component value is calculated in the measurement computation circuit 1.

In the above description, mainly the measurement object such as a storage battery, but the measurement circuit and the calculation method can be easily conceived to measure a measurement element suitable for another measurement object such as electrolytic condensate. In addition, by using the technical basic idea of the present invention can be applied to a portable measuring device through a normal level of deformation or design change or by applying a slight modification to be suitable for the on-line measuring device, the measuring circuit can be designed.

As shown in FIG. 3, an embodiment of the present invention, the technical idea of the present invention can be introduced into an on-line measuring device. In this case, the sinusoidal pulse wave discharge current generated in the pulse wave discharge circuit 2 is a current. From the current sensing means (4 or 5a to 5n) which are controlled to flow to each battery unit or battery cell under connection through the connecting means 21, and are installed block by block between the output terminal of the pulse wave discharge circuit 2 or each battery column. The circuit can be configured to detect the measurement current signal.

The measured current signal sensed by the current sensing means provided for each block between each row of batteries includes a charging current I _CH when sensing the measured current signal by the current sensing means 5a to 5n in FIG. 3. Therefore, this is indicated as an alternating current (I _B ).), The charging current (I _CH ) supplied by the charging device, the charging ripple current (I _RP ) flowing according to the charging ripple voltage, and the pulse wave discharge circuit ( The pulse wave discharge current I _SD flowing from the source terminal of the 4-terminal network from 2) is included.

Therefore, a new implementation of a multi-faceted algorithm or a known ripple cancellation algorithm can be employed to eliminate the influence of the charging current I _CH or the charging ripple current I _RP generated during charging.

The switching means 20 is connected to the measurement operation circuit 1 and controlled in conjunction with the current connection means 21 so as to sense the measurement current signal from the current sensing means 4 or 5a to 5n and the measurement operation circuit 1. It is preferably applied to the on / off (On / Off) by the MPU of the embedded system (16). The switching means 20 and / or the current connection means 21 may be configured as a relay means including an analog switch.

As the pulse wave discharge circuit 2 is operated to discharge the heat of the battery under measurement, a pulse wave discharge current I _SD , which is a measurement current signal, flows. When the measured current signal is larger than necessary, the object to be measured is measured. May adversely affect the battery.

Therefore, the output voltage of the pulse wave discharge circuit 2 should be controlled by adopting a sinusoidal PWM switching control method or a linear voltage control method to control the magnitude of the output current so that the output voltage of the pulse wave discharge circuit 2 can be limited to a predetermined size according to the characteristics of the battery cell. desirable.

Also, Among the impedance voltage (V _IS ) generated by the measured current signal in the form of sinusoidal pulse wave, charge Even when the harmonic ripple current causes other harmonic components to be included relatively large compared to the measured signal frequency components, without using a known Fourier series conversion or filter means for blocking (filtering) the frequency components of a specific band, An impedance effective component corresponding to a frequency component of the measured current signal may be calculated using an algorithm including a filtering program.

4 is a preferred embodiment of the measurement and operation circuit 1, wherein the sine wave discharge current (I _SD ) is a current such as a classifier, a resistor of a classifier function, or a DC current sensing current transformer (DC CT) in the form of a Hall element. It is measured by the sensing means 4 or 5a-5n.

In addition, the sinusoidal pulse current discharge current I _SD obtained through the current sensing means 4 or 5a to 5n is preferably buffered or amplified through the differential amplifier circuit 8. The signal buffered or amplified by the differential amplifier circuit 8 is input to the A / D converter 15 of the embedded system.

Since the sine wave discharge current (I _SD ) of the sinusoidal wave shape includes a DC discharge component, it is possible to more accurately calculate the magnitude of the measured current signal by removing the DC charging current component through the DC cuffing circuit 9. desirable.

If the DC current component is minutely included in the sine wave discharge current I _SD measured by the current sensing means 4 or 5a to 5n, the DC cuffing circuit 9 is not used. Instead, the measured current signal can be directly input to the A / D converter to have the effect of completely removing the DC current component during the impedance effective value calculation process through the calculation program.

In addition, the frequency of the measurement current signal required in the measurement operation step in order to avoid the complexity of the program during the internal impedance calculation and to increase the accuracy is generated by the frequency of the clock pulse 19 generated by the MPU in the embedded system 16 or by dividing it. It is preferably configured to be synchronously controlled with the frequency signal.

In addition, the terminal voltage Vp of the battery cell is obtained by superimposing an impedance voltage V _IS component on the internal voltage V _E of the battery as the measured current signal of the sine wave discharge current of the sine wave shape flows.

Since the impedance voltage V _IS component is very fine compared to the terminal voltage Vp, the DC component through the DC cuffing circuit 11 so that the impedance voltage V _IS component is not saturated in the signal amplification process. It is highly desirable to completely eliminate the signal before signal amplification.

At this time, the terminal voltage (Vp) is converted to an appropriate signal level in the voltage amplifier means or the differential amplifier circuit having an input circuit isolation function and then the DC component can be completely removed by the DC cuffing circuit (11). In general, the DC cuffing circuit 11 may be configured as an operational amplifier having a resistor and a capacitor.

According to an embodiment of the present invention, the impedance voltage (V _IS ) signal converted into the AC level is passed through a known filter means 12 only a frequency of a band similar to the frequency component of the measured current signal, and the amplification circuit group 13 It is desirable to be amplified to the optimal signal level that can be input to the A / D converter (15).

The measured current signal of the sine wave component included in the pulse wave discharge current and the internal impedance voltage V _IS signal corresponding thereto are converted into a digital signal by the A / D converter 15. The internal impedance effective component value is calculated by performing an operation program algorithm of a micro controller unit (MCU).

In addition, the A / D converter 15 has a plurality of analog MUX on the input side, so that the measurement signal of the pulse current discharge current and the impedance voltage (V _IS ) signal are input to the A / D converter 15. It is entered in the channel MUX. Incidentally, in order to measure the battery cell voltage, it is preferable that the output of the differential amplifier circuit 10 is input to the MUX which is the input channel of the A / D converter 15 through the DC filter 14.

In addition, the differential amplifier circuit 10, the DC coupling circuit 11 and the filter means 12 for measuring the impedance voltage (V _IS ) signal of the battery cell is Utility Model Application No. 20-2003-0037800 of the Republic of Korea And another embodiment can be configured with reference to the corresponding technical gist of Patent Application No. 10-2004-0099962.

In addition, another embodiment of the embedded system 16 including a combination configuration of the amplification circuit group 13, the A / D converter 15 by applying a known technique such as Patent Application No. 10-2003-0025823 Can be configured.

In addition, the filter means 12 may be composed of a hardware circuit having a capacitor, a resistance element, an operational amplifier, or an integrated circuit element such as an SCF, and has a narrow bandwidth bandpass having a very narrow bandwidth. Designed to have the filter characteristic, the maximum gain is obtained only at the designated resonant frequency fr, and the attenuation characteristic for frequencies other than the fundamental frequency is designed to be the maximum, thereby minimizing the influence on harmonic noise or charging ripple current during impedance calculation. .

Configured as above By filtering only the frequency component similar to the impedance voltage V _IS component through the filter means 12, the internal impedance corresponding to the measured frequency component or its effective value can be easily calculated according to the effective calculation formula.

Also configured as above It is possible to calculate the internal impedance by precisely calculating only the waveform of the measured frequency component through Fourier series conversion (FT) without using the filter means 12. However, this requires a high speed A / D converter and requires a lot of computation time. In reality, the Fourier series transformation is not effective. Therefore, it is preferable to efficiently calculate the internal impedance effective component using a known wave filter means or a synchronous detection algorithm without performing the Fourier series transformation.

5 shows the output voltage waveform of the pulse wave discharge circuit and the waveform of the pulse wave discharge current I _SD outputted through the discharge circuit. As shown in FIG. 5, the pulse wave discharge circuit is generally controlled to have a slight DC discharge current _Δ I _I so as to exclude the sinusoidal distortion during the half cycle. The instantaneous value of the half cycle must be controlled to be close to zero to minimize the heat generation of the pulse wave discharge circuit 2.

More specifically, since the DC discharge current I _DC included in the pulse wave flux is a component that does not contribute to the generation of an internal impedance voltage signal, the output amplification means 34 of the pulse wave discharge circuit must be controlled to almost zero (34). ) And heat generation of the discharge load (R _L ) can be reduced and the control loss is minimized accordingly.

Therefore, when the instantaneous peak value of the sine wave current is 2 + _Δ I _I in FIG. 5, since the average value of the pulse wave current corresponds to 1+ _Δ I _I , the pure discharge current _Δ I _I It is preferable to control the current size corresponding to almost zero.

Hereinafter, a detailed configuration of the pulse wave discharge circuit and its operation will be described as an embodiment of the present invention.

Figure 6 is an embodiment of the pulse wave discharge circuit of the present invention,

7 is another specific embodiment of the pulse wave-shaped discharge circuit in the present invention.

8 is another embodiment in which the PWM switching control function of the pulse wave discharge circuit is introduced in the present invention.

The pulse wave discharge circuit 2 basically includes a sine wave generating means 31 and a linear amplifying means 33, and may further include an output amplifying means 34 in consideration of the magnitude of the measured current signal. .

Here, the linear amplifying means 33 or / and the output amplifying means 34, the triangle wave generator circuit 41, the modulation circuit 42, the drive circuit 43, the PWM switching control means 44 according to the technical judgment of the designer ) And a sinusoidal wave filter means 45 may be replaced with a PWM switching control circuit to configure its function.

In addition, the signal isolating means 32 may be further included for the purpose of electrically insulating the input control unit of the pulse wave discharge circuit and the circuit under test.

The sinusoidal wave generating means 31 has a function of generating a sinusoidal wave by a clock signal generated from the MPU of the measurement computation circuit 1. In general, a signal corresponding to the clock can be generated by generating a required frequency by a self-contained clock generator composed of a known passive element. However, in one embodiment of the present invention, the basic of the MPU of the measurement operation circuit 1 Since the sine wave generated by the clock and the sinusoidal wave generating means 31 is synchronized to facilitate the calculation of the internal impedance value in the MPU, the corresponding clock signal of several times to several tens of the selected measurement current signal frequency is measured. It is preferable to generate the sinusoidal wave measurement current signal using it.

At this time, after the clock pulse output from the MPU or the basic pulse control signal of the MPU is output, the capacitor C1 and the resistor R4 or R so that the sine wave is immediately generated and the sine wave can be restored to its normal size as soon as possible. And parallel resistance of R4) are selected properly.

In addition, the control power supply of the sine wave generating means 31 preferably uses the same power supply as that of the measurement operation circuit 1 (usually +12 to + 5V), and the linear amplification means 33 And / or the operating power supply of the output amplifier means (34) is generally measured object circuit (eg, a battery or a storage battery cell unit packed column) of the full + - and the DC voltage V _{B +} V _{B -} so to be connected to, to the input side control circuit portion and the to-be-output of the measured sine-wave generating means (31) for electrical insulation of the water circuit which is photo coupler and insulated from each other electrically through the same signal isolation means 32 desirable.

In addition, since the output terminal (output side of the optical transistor) of the signal insulating means 32 has a relatively low rated voltage, the voltage limiting means 37 having a voltage limiting function or a constant voltage control function is provided. Operating power (V _{B +} and V _{B -} or by decreasing the distribution) is preferred to be connected to an output of said signal isolation means (32).

The sinusoidal wave obtained by the sinusoidal wave generating means 31 is input to the non-inverting terminal of the operational amplifier 36 via a cuffing condenser and the reference voltage is input to the inverting terminal of the operational amplifier 36 to amplify the sinusoidal signal. do.

The output of the operational amplifier 36 is connected to the input of the output transistor (base in the case of NPN transistor, gate in the case of FET) terminal in the form of a Darlington amplifier circuit so that the output current is amplified, a sinusoidal wave of an appropriate size A pulse wave waveform with current can be obtained and an internal impedance voltage signal of a corresponding magnitude can be obtained.

As one embodiment, the amount of the voltage level which is added to the non-inverting terminal (+) input of the operational amplifier 36 corresponding to the pure water discharge current _(△ I _I) shown in Figure 5 by adjusting by the variable resistor (VR) to zero ( Control and adjust with 0). The amount corresponding to the pure discharge current (I _DC ) is the operating power (V _{B +} and V _B- ) will change according to the size.

9 to 10 show another embodiment of the present invention. 9 is a schematic diagram of another pulse wave-shaped discharge circuit, and FIG. 10 is a pulse wave discharge circuit of a square wave clock pulse input type.

The clock pulse 19 output from the MPU in the embedded system 16 is generated in the form of a square wave having the same frequency as the sine wave, and is electrically insulated by a known signal isolating means 32 to form a square wave-sine wave converting means ( 40).

Square-sine wave converting means 40 is composed of an operational amplifier 36, which is an active element, and a resistor R13, a resistor R14, a resistor R15, a capacitor C11, and a capacitor C12, which are almost the same as a known band active filter. Therefore, the sine wave output signal having the same characteristics as the band pass filter and converted and output by the square wave-sinusoidal wave converting means 40 is synchronized with the square wave clock pulse.

By appropriately selecting the passive components resistors R13, 14, R15, condenser C11 and condenser C12, the resonance characteristics of the band active filter can be obtained so that the attenuation ratio is minimized with respect to the fundamental frequency of the square wave (maximum output for the fundamental frequency component). Can be.

As such, in the signal insulating means 32 The electrically insulated square wave clock pulse is converted into a sinusoidal current signal synchronized with the square wave clock pulse signal by the square wave-sinusoidal wave conversion circuit 40, and is outputted in this manner. The discharge current is to operate to flow.

In addition, the circuit operating power supply (V _{B +} and DC voltage) of the measured object (in the case of a battery, a battery cell or a bundle of cells). In order to prevent the sinusoidal output waveform amplified and outputted by the operational amplifier 36 from being saturated even when V _B− ) is minimum, the first resistor R11 and the second resistor R12 are used to prevent the clamping. Circuit operating power (V _{B +} and V _B− ) is divided to cause the divided voltage thereof to be input to the input terminal of the square wave-sine wave converting means 40.

The circuit operating power (V _{B +} and Since the divided voltage of V _B- ) is used as a control voltage of the signal insulation means 32, it is advantageous to use a lower voltage specification of the signal insulation means 32.

In the general band active filter circuit, the non-inverting input terminal of the operational amplifier 36 is connected to a negative control power source, so that its output waveform is pure AC component, but the square-sine wave converting means 40 is the operational amplifier. The voltage level signal of the magnitude required for the non-inverting input terminal (36) and the common connection point of the resistor R14 (for example, the control power supply of the operational amplifier or the operating power supply of the circuit under test (VB ₊ Voltage level signal obtained by dividing V _B- ) to shift the voltage level of the center point of the sine wave signal to the center point (50% of the operating power) of the circuit operating power of the measured object. As a result, a sinusoidal wave form waveform can be obtained.

In an embodiment of the present invention, the circuit operating power (V _{B +} and V _{B -),} the potentiometer (VR10) or fixed resistor divided by by applying them to the non-inverting input terminal of the operational amplifier 36, the up / down cycle center point voltage level is a measured circuit operating power supply of the sine wave to (V _{B +} Wow V _{B -} central point (the amount corresponding to the pure water discharge current is controlled to be displayed in the match 50%) of Figure 5 of the operation power source size _(△ I _I) a) it can be controlled to almost zero.

In this way, the operating voltage of the circuit under test (V _{B +} and Since the voltage input to the square-sine wave conversion circuit 40 is adjusted according to the size of V _B- ), the center point voltage level of the sine wave is automatically adjusted. 36), it is possible to minimize the heat of the output amplifying means 34 and / or the discharge load (RL).

When the sine wave signal, which is an analog signal, is electrically insulated by the signal isolating means 32 using the optical element, the output current ratio transmission characteristic of the sine wave is changed in the active operation region of the signal isolating means 32 due to the ambient temperature. It may change depending on the ambient temperature. However, in the case where the square wave clock pulse signal, which is a digital signal, is electrically insulated by the signal isolating means 32 as in the embodiment as shown in FIG. 10, the output current ratio of the signal isolating means 32 using the optical element is transmitted. Even if the characteristic is changed, the digital signal does not use the active operation region, so that the magnitude of the sine wave output can be prevented from changing with the ambient temperature.

In this way, the isolated sinusoidal output signal is amplified in current magnitude through the linear amplifying means 33 or the output amplifying means 34 having a power amplifying circuit function, and the circuit of the measured object (for example, a battery string or a battery cell bundle). Operating voltage (V _{B +} and V _{B -)} are so linear amplifier means (33) or an output amplifier means (34) and the configuration is connected to the load acts on the output terminal of the power amplification circuit as, pulsating wave discharge circuit 2 is a measured object (heat Examples battery Alternatively, the power supply of the battery cell is controlled to be discharged in the form of a sinusoidal pulse wave current, and an internal impedance voltage signal can be obtained by the sinusoidal pulse wave current signal being discharged.

Further, it may be more preferable that the output of the sinusoidal pulse wave discharge current is amplified and linearly controlled by an output circuit control element of a commercially available audio amplifier element having the function of the operational amplifier 36.

That is, the general operational amplifier element is usually less than +-15V, so if the total voltage of the battery column to be measured exceeds 15V (for example, when 2V batteries are connected to 6 or more), the general operational amplifier element can be used. Therefore, it is highly desirable to adopt a commercially available audio power amplifier element as the operational amplifier element of the linear amplifying means 33 or the square-wave sine wave converting means 40.

The audio power amplifier device may further have a function of an output amplifying means 34 having a current amplifying function so as to properly amplify and process the amount of output discharge current, and several tens of W class is already commercialized.

An output amplifier means (34) to the output side of the sine wave conversion means (40) and the output circuit can not get the output current signal of satisfactory size by side control devices only, linear amplification means (33) or a square wave of the audio Amphoe element Additional connections can be made to amplify the output current to the required size.

V_L)에 해당된 영역을 최소화할 수 있게 설계하는 것이 바람직하다. The load resistor R _L connected to the output transistor emitter terminal (source terminal in the case of a MOS FET) of the output amplifying means 34 has a loss voltage (A) so as to minimize thermal loss when the output transistor is operated in an active region.

It is desirable to design so that the area corresponding to V _L ) can be minimized.

V_L)을 최소화되게 조정할 수 있다.In order to minimize the thermal loss due to the active area operation, the operation of the circuit under test can be performed by appropriately adjusting the magnitude of the output of the operational amplifier 36 or the connection resistance of the output side or the amplification degree H _fe of the output amplifying means 34. The loss voltage corresponding to the difference between the voltage (V _{B +} ) and the maximum value of the sinusoidal output voltage (

V _L ) can be adjusted to minimize.

In one embodiment of the present invention as a circular circuit, currently commercialized 20W class An audio power amp is used, which has a maximum operating voltage of 16V to 60V and a current limit of around 3A. As commercialized models thereof, audio power amplifier devices having equivalent characteristics such as LM1875 or LM4755 may be mainly used.

In addition, as another embodiment, a PWM switching control method may be employed to generate a sinusoidal discharge current. 8 shows a conceptual circuit employing a PWM switching control scheme.

In the PWM switching control system, the sinusoidal wave signal obtained from the sinusoidal wave generating means 31 and the triangle wave signal obtained from the known triangle wave generating circuit 41 are compared with each other in the modulation circuit 42 to form a sinusoidal PWM switching control signal, and the base driving circuit The switching control signal is applied to the semiconductor switching element input side of the PWM switching control means 44 through the furnace 43 to control the switching of the semiconductor switching device and generate a PWM output waveform to generate an output current having a current form similar to a sine wave.

The sinusoidal filter means 45 serves to filter the PWM switching output waveform so that it does not contain harmonic currents by switching, as closely as possible to the sinusoidal waveform.

In addition, by using the basic clock signal generated from the MPU to make the triangular wave required in the triangular wave generating circuit 41, and further divides the basic clock signal to the frequency divider circuit 46 to sinusoidal wave frequency in the sinusoidal wave generating means 31 It is desirable to control to generate.

Switching the semiconductor device at a high frequency in order to generate a PWM switching waveform to generate an output current in the form of a sinusoidal wave increases the switching loss. When designing the pulse wave discharge circuit 2 using the PWM switching waveform, considering the characteristics of the current commercially available semiconductor switching device, the modulation frequency of the PWM pulse is appropriately set within the range of 10 KHz to 40 Khz, so that switching loss or control It is necessary to determine the characteristics optimally.

In the above embodiments of FIGS. 6 to 10, current measuring means 35 such as a classifier or a current sensor is installed at the final output circuit terminal of the pulse wave discharge circuit 2 to sense the amount of output discharge current. Input to the MPU, and the signal is fed back to the sinusoidal wave generating means 31, the linear amplification means 33, or the square wave-pulse wave generating means 40 to control the feedback so that the amount of output discharge current is constant. More preferred.

As described above, an internal impedance voltage V _IS signal can be obtained by flowing a sinusoidal pulse wave measurement current signal through the object under test. In addition, the sensing current signal of the sinusoidal pulse ripple shape is detected by the current sensing means, and included in the high frequency ripple voltage generated by the measurement current signal and the charging ripple current component From the internal impedance voltage (V _IS ) signal and similar frequency components, known synchronous detection algorithms can be used to accurately calculate the internal impedance of the workpiece or its effective value.

) 및 손실각 tanδ값을 연산할 수 있다.In addition, by using the above-described technical spirit as it is, the sine wave pulse current measurement current signal of the sine wave shape as an electrolytic capacitor as a method for diagnosing the aging of the electrolytic capacitor that can be easily aging of the power converter components. The internal impedance of the electrolytic capacitor, or its effective value, is calculated using the internal impedance voltage signal component induced by

) And the loss angle tan δ can be calculated.

Hereinafter, a description will be made of whether a known synchronous detection algorithm can be applied as an embodiment of the present invention. The basic principle of the synchronous detection operation is to determine a constant integral period T _D for a sine wave function having an arbitrary frequency or an integral frequency thereof, and perform periodic integration with its integral period T _D. As shown in Eq. (2), for any arbitrary harmonic component, its periodic integration result is zero, and this principle can be used to eliminate all sinusoidal AC component terms appearing in the calculation process. will be.

(1)

(One)

(2)

(2)

Using this mathematical principle, the frequency of the measured current signal is determined to be an arbitrary multiple of the frequency (60 Hz or 50 Hz) ω of the commercial power supply, and each calculation term m ₁ , m ₂ , m ₃ and m ₄ is calculated. By integrating the calculation result with a constant integral period T _D , all AC component terms excluding DC components are zero, and M ₁ , M ₂ , M _3, and M ₄ terms consisting of DC components are obtained. Through the calculation process by the synchronous detection method, the impedance effective value can be calculated accurately and simply.

More specifically, the calculation term m1, m2, m3 from the AC voltage (V _SM ), the measured current signal, the cosine wave C1 and the sine wave S1, which are internal impedance voltage signals in which the high frequency ripple voltage V _RP is mixed. and calculating the m4, respectively, of all frequency components forming the alternating voltage (V _SM) or the measured current signal mutual addition and a subtraction to obtain the greatest common divisor between a result of the value interval corresponding to the frequency of the greatest common divisor or the When the constant integral period T _D necessary for the operation is determined as an integer multiple of the period, and the operation terms m1, m2, m3, and m4 are integrated during the constant integration period T _D , the value obtained as the integral result is Since the DC component of equations (3) to (6) is multiplied by the integral period (T _D ), the resultant value is then divided by the integral period (T _D ), as shown in equations (3) to (6) below. which may be the indication M _1, M _2, M ₃ and M ₄ Can.

(3)

(3)

(4)

(4)

(5)

(5)

(6)

(6)

When the following equation (7) is calculated using the above equations (3) to (6), the result value of the equation (7) is equal to the effective value of the internal impedance, so that the following equation (7) can be used simply. The effective internal impedance can be found.

                                                                   (7)

는 임피던스 전압(V_IS) 파형의 실효값이며

는 정현파 교류전류의 실효값로 표시될 수 있다.At this time, 2A is the maximum value of the impedance voltage (V _IS ) waveform and 2B is the maximum value of the sinusoidal AC current. therefore,

Is the effective value of the impedance voltage (V _IS ) waveform

Can be expressed as the effective value of the sinusoidal AC current.

In addition, in order to reduce the calculation time required to calculate the impedance effective resistance, the maximum common factor between the results of the subtraction subtraction calculation should be minimized. Therefore, the frequency of the measurement current signal supplied to the measurement target is set to a high frequency ripple voltage (V). _RP ) is selected to be different from the frequency of any harmonic voltage constituting the _RP ), but the frequency band is primarily selected by the designer's decision, and each harmonic constituting the high frequency ripple voltage (V _RP ) is arranged in order of magnitude 1 The integrating period T _D can be reduced to a minimum by selecting the frequency of the measured current signal to be equal to the frequency average value of two adjacent harmonics within the selected range. Of course, if the integral period T _D is integrated by the integral multiple of the selected period, the amount of calculation increases, but there is an advantage that the error in the measurement operation can be reduced.

In addition, the frequency of a commercial power supply is generally used at 60 Hz or 50 Hz. Therefore, when the fundamental frequency of the measurement signal supplied to the object under test is set to an arbitrary multiple of 5 Hz or 10 Hz according to the above-described technical concept, all AC components constituting the impedance voltage or the sinusoidal AC current are independent of the frequency of the commercial power supply. By adding and subtracting frequencies mutually, the maximum common divisor of the result of addition and subtraction is determined to be 5Hz or 10Hz, and if the period is integrated over a period corresponding to 5Hz or 10Hz or an integer multiple of the period, all AC component terms are zero. Since M ₁ , M ₂ , M _3, and M ₄ terms consisting of direct current components can be obtained (0), it is possible to use a measurement current signal of the same frequency regardless of the frequency of the commercial power supply at 60 Hz or 50 Hz.

Then, the internal impedance according to the present invention or the effective component measurement calculation method thereof according to the present invention will be described in detail with reference to the accompanying drawings.

11 is a flow chart showing the flow of the method of measuring the internal impedance or its effective component (internal resistance or loss angle) according to the present invention.

First, as shown in Fig. 11, the measurement operation method according to the present invention uses a linear voltage control method or a sinusoidal PWM switching control method so that the measured current signal of the sine wave discharge current in a sine wave shape flows to the object to be measured. To control (S301).

At this time, the frequency of the measured current signal of the pulse wave discharge current of the sinusoidal shape is equal to any one selected from 0.5 times, (n + 0.5) times, 5 Hz or an integer multiple thereof, or 10 Hz or an integer multiple thereof of the commercial power frequency of 50/60 Hz. It is preferable that it is set.

In addition, the measurement signal of the pulse current discharge current of the output controlled sinusoidal wave shape is supplied to the measured object (S302).

Then, the internal impedance voltage component and the similar frequency component of the measured object detected by the sine wave-shaped pulse current discharge current measurement signal are passed (S303).

Next, the internal impedance or its effective value (or loss angle) is calculated using the measured current signal and the impedance voltage signal component (S304).

Preferred embodiments of the present invention described above are disclosed for the purpose of illustration, and various substitutions, modifications, and changes within the scope without departing from the spirit of the present invention for those skilled in the art to which the present invention pertains. It will be possible, and such substitutions, changes and the like should be regarded as falling within the scope of the following claims. In addition, even if not specifically presented in the preferred embodiment of the present invention can be calculated by measuring the internal resistance or internal impedance value of the object to be measured, such as a battery or electrolytic condensate using the technical idea presented in the present invention.

The present invention eliminates the need for a voltage source or a current source for generating sinusoidal currents by using a measurement algorithm similar to the AC current injection method, thus eliminating the need for a control power supply for the sinusoidal wave generation circuit. It has the advantage of being simplified.

Therefore, it is possible to improve the measurement operation circuit while having the same size hardware circuit. Therefore, three quaternary systems obtained by the formal result obtained by the internal equivalent circuit without measuring cosθ, which is the phase difference between the measured current signal and the impedance voltage signal, are measured. From the equation, it is also possible to easily construct a hardware circuit that can obtain the internal resistance or capacitor component values of each element of the battery equivalent circuit represented by three unknown terms Rs, Ro, and Xc.

) 및 손실각 tanδ값을 연산할 수 있다.In addition, the sine wave-shaped pulse wave measurement current signal flows from the electrolytic capacitor, and by using the internal impedance voltage signal component induced therein, the ESR value (the internal resistance component of the electrolytic capacitor used in the power conversion device, etc.)

) And the loss angle tan δ can be calculated.

In addition, it is possible to use all the RLC series circuit components of the internal equivalent circuit of the battery by applying a measuring circuit similar to the conventional alternating current injection method or a known measuring operation algorithm using the technical idea of the present invention. It will be more likely.

In addition, although not specifically presented in a preferred embodiment of the present invention, it is possible to analyze the aging state of the object to be measured by measuring the internal resistance or the loss angle, such as electrolytic condensate using the technical idea presented in the present invention.

1 is a conceptual diagram of a method for measuring internal impedance by discharge current of a pulse wave shape of the present invention.

Figure 2 is a schematic diagram of the internal impedance measurement method by the discharge current of the pulse wave shape as a representative embodiment of the present invention.

3 is a configuration diagram applied to an on-line measuring apparatus according to an embodiment of the present invention

Figure 4 is an embodiment of the measurement operation circuit of the present invention.

5 is a pulse wave-shaped discharge current waveform and an output voltage waveform of a pulse wave discharge circuit in the present invention.

6 is a schematic diagram of a pulse wave-shaped discharge circuit according to an embodiment of the present invention.

Figure 7 is another embodiment of the pulse wave discharge circuit in the present invention.

8 is a circuit diagram of a pulse wave generating circuit using a PWM switching control method according to an embodiment of the present invention.

9 is a schematic diagram of another discharge circuit of a pulse wave shape which is an embodiment of the present invention.

10 is a pulse wave discharge circuit of a square wave clock pulse input type according to another embodiment of the present invention.

11 is a step of controlling the sine wave discharge current of the sinusoidal shape in the present invention

Claims (18)

In calculating the internal impedance of an object under test or its effective value (or loss angle), Controlling a measurement signal of a sine wave discharge current having a sinusoidal wave shape (a measurement current signal in the form of a sine wave pulse wave) to flow through the object to be measured; Obtaining an internal impedance voltage signal of the measured object generated by the measured current signal in the form of the sinusoidal pulse current; And Calculating an internal impedance or an effective value thereof using the measured current signal and the internal impedance voltage signal; Internal impedance measurement calculation method comprising a. The method of claim 1, And measuring the output current of the sine wave pulse current in a linear manner using an active operation region of a transistor. The method of claim 1, The measurement method of the sinusoidal pulse current form the internal impedance measurement operation method characterized in that the output is controlled by the sinusoidal PWM switching control method. The method according to any one of claims 1 to 3, And measuring the frequency of the sinusoidal pulse current in the form of a pulse, whose frequency is synchronized with a clock signal output from the MPU. The method according to any one of claims 1 to 3 The frequency of the measured current signal in the form of a sinusoidal wave current is determined to be equal to any one selected from 0.5 times, (n + 0.5) times of commercial power frequency, 5 Hz or an integer multiple thereof, or 10 Hz or an integer multiple thereof. Measurement operation method. The method according to any one of claims 1 to 3, Computing the internal impedance or its effective value, Obtaining a maximum common divisor between the measured current signal frequency components in the sine wave pulse current form and all harmonic frequency components forming the AC voltage (V _SM ) and mutually added and subtracted from each other; And, And determining a constant integral period T _D necessary for the calculation as a period corresponding to the frequency of the greatest common divisor or an integer multiple of the period. An internal impedance measurement calculation method for calculating an internal impedance of an object under test or an effective value thereof (or a loss angle thereof) through a known synchronous detection algorithm. In calculating the internal impedance of an object under test or its effective value (or loss angle), Generating a measured current signal in the form of a sinusoidal pulse current to generate an internal impedance voltage component Pulse wave discharge circuit; Current sensing means for detecting a measured current signal in the form of a sinusoidal pulse current flowing through the object to be measured; And A measurement operation circuit for calculating an internal impedance or an effective value thereof by using the measured current signal in the form of a sinusoidal wave current and an impedance voltage (V _IS ) signal of an object to be measured; Internal impedance measurement calculation device comprising a. In measuring and calculating the internal impedance of the battery or its effective value, A pulse wave discharge circuit for generating a discharge current in the form of a sinusoidal pulse stream as a measurement current signal and flowing the resultant battery column or cell to be measured; Current sensing means (5a to 5n) provided at an output end of each of the battery rows or current sensing means (4) provided at an output end of the pulse wave discharge circuit; And Current connection means for switching the output current signal of the pulse wave discharge circuit to each of the storage cells; And A measurement operation circuit calculating an internal impedance or an effective value thereof by using the measurement current signal and an impedance voltage V _IS signal of a battery cell; Internal impedance measurement calculation device of a storage battery including a. The method according to claim 7 or 8, The measurement operation circuit, An input end circuit of the current sensing means for sensing a measured current signal in the form of a sinusoidal pulse current; A differential amplifier circuit for dividing or insulating amplifying the terminal voltage Vp of the object under test; And A DC coupling circuit for filtering only the internal impedance voltage V _{IS of the} object under test from the terminal voltage Vp; And An A / D converter for converting the measured current signal in the form of the sinusoidal pulse current and the analog signal which is the output of the DC coupling circuit into a digital signal; Internal impedance measurement calculation device comprising a. The method of claim 9, And an filtering means for filtering the impedance voltage (V _IS ) component and similar frequency components necessary for the measurement from the internal impedance voltage (V _IS ). The method according to claim 7 or 8, The pulse wave discharge circuit, Sinusoidal wave generating means (31) for generating a sinusoidal wave; and Linear amplification means for inputting a sinusoidal wave obtained by the sinusoidal wave generating means and linearly amplifying it; Internal impedance measurement calculation device comprising a. The method according to claim 7 or 8, The pulse wave discharge circuit, A square wave-sine wave conversion circuit for receiving a clock pulse having a square wave shape and converting it into a sine wave; And, Output amplifying means for current amplifying the operational amplifier output of the square-sine wave conversion circuit; Internal impedance measurement calculation device, characterized in that configured to include. The method according to claim 7 or 8, The pulse wave discharge circuit, Sinusoidal wave generating means (31) for generating a sinusoidal wave; A modulation circuit 42 for generating a sinusoidal PWM switching control signal by comparing the sinusoidal wave signal obtained by the sinusoidal wave generating means 31 with the triangle wave signal obtained from a known triangle wave generator circuit 41; And PWM switching control means (44) controlled to be switched by the sinusoidal PWM switching control signal; Internal impedance measurement calculation device comprising a. The method of claim 11, The pulse wave discharge circuit, And an signal isolation means for electrically insulating the input control circuit portion from the circuit under operation. The method of claim 11, The pulse wave discharge circuit, And an output amplifying means for amplifying the measured current signal output from the linear amplifying means. The method of claim 12, The pulse wave discharge circuit, And an signal isolation means for electrically insulating the input control circuit portion from the circuit under operation. The method of claim 12, Square wave-sine wave conversion circuit, By applying a voltage level signal of a required magnitude to the common connection point of the non-inverting input terminal of the operational amplifier and the resistor R14, the sinusoidal output signal is controlled to be shifted. An internal impedance measuring and calculating device characterized in that the object to be measured. The method of claim 12, Square wave-sine wave conversion circuit, And an operational amplifier, resistors R13 to R15, a capacitor C11, and a capacitor C12, and having an active band characteristic filter.

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