KR20070072830A - Microstrip array antenna - Google Patents

Abstract

A microstrip antenna has a single dielectric layer with a conductive ground plane disposed on one side, and an array of spaced apart radiating patches disposed on the other side of the dielectric layer. The radiating patches are interconnected with a feed terminal via stripline elements. Responsive to electromagnetic energy, a high-order standing wave is induced in the antenna and a directed beam is transmitted from and/or received into the antenna. A dual-mode embodiment is configured such that standing wave nodes occur at the intersection of orthogonally situated striplines to minimize cross- polarization levels of the signals and the cross-talk between the two modes of operation.

Description

Microstrip Array Antenna {MICROSTRIP ARRAY ANTENNA}

A single dielectric layer multipatch, microstrip array antenna design included in a leaky cavity for distributing EM (electromagnetic) power between radiating patches and a source.

The present invention generally relates to antennas and, more particularly, to microstrip array antennas.

The number of direct satellite broadcast services has increased significantly worldwide, and thus the global demand for antennas with the capacity to receive these broadcast services has increased. This increased demand has typically been met with reflector or "dish" antennas known in the art. Reflector antennas are typically used in residential environments to receive broadcast services such as transmission of television channel signals from stationary or equatorial satellites. However, reflector antennas have some disadvantages. For example, it is bulky and expensive for home use. Also, in reflector antennas, feed spillover and aperture blockage by a feed assembly are inherent, which significantly reduces the aperture efficiency of the reflector antenna, typically about 55 This results in an opening efficiency of only%.

Alternative antennas, such as microstrip antennas, overcome many of the disadvantages associated with reflector antennas. For example, microstrip antennas require less space, are simpler and cheaper to manufacture, and are more suitable for printed circuit technology than reflector antennas. Microstrip array antennas, ie microstrip antennas with arrays of microstrips, can be used in applications that require high directivity. However, microstrip array antennas typically require complex microstrip supply networks that contribute significant supply losses to the total antenna losses. In addition, many microstrip array antennas are limited to single polarization and to transmit or receive only linearly polarized beams. This drawback is particularly important in many areas of the world where broadcast services use only circularly polarized beams. In such cases, service beneficiaries must rely on less efficient and more expensive, bulky reflector antennas, or microstrip array antennas using polarizers. However, polarizers impose additional power loss on the antenna and create a relatively poor quality radiation pattern. In addition, when dual polarization is required, two antennas of single polarization are required.

Thus, there is a need for a compact antenna that is inexpensive, simple to manufacture, and has high aperture efficiency, which does not require a complex supply chain and is either a single or double polarized linearly or circularly polarized beam. It should be easily adaptable to transmit and / or receive.

Accordingly, the present invention has a low cost and compact antenna which has high aperture efficiency, does not require a complicated supply network, can be easily applied to transmit and / or receive linearly polarized or circularly polarized beams, and has a dual-polarized performance. to provide. To this end, the microstrip antenna of the present invention comprises a single dielectric layer having a conductive ground plane on one side and an array of spaced radiating patches disposed on the other side of the dielectric layer to form a leakage cavity. In response to electromagnetic energy, a directional beam is received at and / or transmitted from the antenna.

For a more complete understanding of the present invention and its advantages, reference is now made to the following description in conjunction with the accompanying drawings.

1 is a perspective view of a planar array antenna;

FIG. 2 is an elevation cross-sectional view of the antenna of FIG. 1 taken along line 2-2 of FIG.

3 is a perspective view of a variant embodiment of the planar array antenna of FIG.

4 is a plan view of a flat array antenna;

5 is a cross-sectional view of the antenna of FIG. 4 taken along line 5-5 of FIG.

6 is a plan view of a planar array antenna;

7 is a cross-sectional view of the antenna of FIG. 6 taken along line 7-7 of FIG.

8 is a plan view of a planar array antenna;

9 is a cross-sectional view of the antenna of FIG. 8 taken along line 9-9 of FIG.

10 is a plan view of a planar array antenna;

11 is a cross-sectional view of the antenna of FIG. 10 taken along line 11-11 of FIG.

12 is an enlarged view of a portion of the antenna of FIG. 11 surrounded by line 12 of FIG.

13 is a plan view of a planar array antenna;

14 is a cross-sectional view of the antenna of FIG. 13 taken along line 14-14 of FIG.

15 is an enlarged view of a portion of the antenna of FIG. 13 surrounded by line 15 of FIG.

16 is a plan view of a planar array antenna;

17 is a cross-sectional view of the antenna of FIG. 16 taken along line 17-17 of FIG.

18 is a plan view of a variant embodiment of the antenna of FIG.

19 is a plan view of a planar array antenna;

20 is a cross-sectional view of the antenna of FIG. 19 taken along line 20-20 of FIG.

21 is a plan view of a planar array antenna;

FIG. 22 is a cross-sectional view of the antenna of FIG. 21 taken along line 22-22 of FIG. 21;

23 is a plan view of a planar array antenna.

FIG. 24 is a cross-sectional view of the antenna of FIG. 23 taken along line 24-24 of FIG.

25 is a plan view of a flat array antenna;

FIG. 26 is a cross-sectional view of the antenna of FIG. 25 taken along line 26-26 of FIG. 25;

27 is a plan view of a planar array antenna;

FIG. 28 is a cross sectional view of the antenna of FIG. 27 taken along line 28-28 of FIG. 27;

29A and 29B are plan views of planar array antennas.

30 is a cross-sectional view of the antenna of FIGS. 29A and 29B taken along line 30-30 of FIGS. 29A and 29B.

FIG. 31 is a bottom view of the microstrip of the antenna of FIG. 30;

32 is a plan view of a planar array antenna;

FIG. 33 is a cross sectional view of the antenna of FIG. 32 taken along line 33-33 of FIG. 32;

34 is a plan view of a planar microstrip directional coupler implementing features of the present invention to couple two EM energy sources to two EM energy destinations.

FIG. 35 is a cross-sectional view of the coupler of FIG. 34 taken along line 35-35 of FIG. 34;

In the discussion of the following figures, members specifically illustrated for clarity are not necessarily drawn to scale, and like or similar members are denoted by the same reference numerals throughout the several views.

Two types of antennas are now described. One is a linear polarized antenna with one supply for single-mode operation. In this embodiment, no cross or crossing stripline conductors are needed, and the structure is simpler. The other is a dual-mode antenna with cross or cross stripline conductors that operate independently of each other and connect patches to the supply connectors.

In a dual mode configuration, the antenna acts as two superimposed antennas. Such an antenna may use two supply terminals where the stripline conductors of one terminal are perpendicular to the stripline conductors of the other terminal. Each patch of the antenna is connected to a stripline conductor in a first orientation at one corner of the patch or at another point in the patch where two orthogonal modes can be excited, and in adjacent directions or points in the second direction ( Orthogonal) orientation stripline conductor. In this embodiment, the placement of patches and stripline conductors causes nodes of standing waves to coincide with the stripline intersection, to reduce cross-polarization levels and crosstalking. The generation of standing wave nodes in each stripline conductor creates a predetermined or pre-defined preferred field distribution.

For maximum directivity of the antenna, it is designed to provide a uniform power distribution between the radiating patches. When configured for uniform field distribution, all patches can have the same physical size, and all interconnected striplines have the same dimensions, which can greatly simplify the design process and reduce manufacturing tolerances. This is in contrast to the prior art design which requires a number of different parameters for the striplines interconnecting the spin patch members to obtain a relatively uniform field distribution between the spin patches for maximum directivity.

On the other hand, in some applications, despite the fact that the directivity can be reduced from the optimal value, it is desirable for the tapered distribution across the radiating patches to reduce sidelobes.

The dual-mode antennas provided herein can make two right-angled linearly polarized radiation, or modify the supply region slightly, so that two right-angled circularly polarized (ie right-handed and left-turned) radiations are available. You can do It will be appreciated that the dual-mode antenna can be used for single-mode operation simply by not using other ports. It will be appreciated that for optimal results, in dual mode antennas, the radiating patches should be two fold symmetrical.

Stripline conductors, alternatively simply stripline in the art, form part of the surface of the leaking cavity and affect the resonant frequency of the cavity while helping to flow power between the radiating patch members. The stripline acts to guide the proper flow of power so that the leaked power is sent, i.e., radiated, in the desired direction, while minimizing other factors to maximize antenna efficiency. In prior art antennas, the striplines act as conductive paths whereby the propagating wave is transmitted from the supply to the radiation patches. In the present invention, the stripline acts as a channel connecting the supply and the patches such that energy flows back and forth to form a standing wave in the channel bridge. As used herein below, the word “stripline” is intended to be applied to any conductive material, other than radiative patches, that is on the dielectric surface opposite the ground plane and further surrounds the cavity, i.e. traveling wave, standing wave. Or to guide the flow of power in the form of a combination of the two.

In view of the various embodiments possible with this single-dielectric layer antenna using both standing and traveling waves, a number of configurations, from simple to complex, are illustrated and discussed in the following paragraphs.

Unless otherwise specified, λ。 should be understood as the wavelength of the beam of EM energy in free space (ie λ。 = c / f, where C is the speed of light in free space and f is the frequency of the beam). , λ _ε should be understood as the wavelength of the EM energy beam in the dielectric medium (ie λ _ε = v / f, where v is the light flux in the dielectric medium). Also, as used herein, members referred to as “strip”, “patch”, “stripline”, “stub”, and “transmission line” are preferably conductive, having a thickness of about 1 mil (0.001 inch). Configure the microstrip Ground planes and edge conductors also preferably have a thickness of about 1 mil (0.001 inch), but can be thicker if desired to give structural support to each antenna (eg, 0.125 inch). Thickness is generally measured in a direction perpendicular to the dielectric surface to which the microstrip, ground plane or edge conductors are respectively bonded.

In addition, unless otherwise specified, the dielectric material used according to the invention (other than cables) is preferably made from a mechanically stable material having a relatively low dielectric constant. The dielectric layer may be appropriately multilayered to provide the desired dielectric constant. Or a composite layer or not, or a single dielectric layer, preferably, gatjiman a thickness of 0.003λ to 0.050λ _{ε ε,} may have a greater thickness for greater bandwidth.

As used herein, referring to a high-order standing wave includes one of the modes of forming a high standing stationary wave other than the basic mode.

In addition, as used herein (unless otherwise specified), ground planes, edge conductors, microstrips (eg, strips and patches), etc., are preferably conductive materials such as copper, aluminum, silver, and / or gold. It includes. For the bonding of such conductive materials to dielectric materials, the present application preferably uses conventional printed circuitry, metallizing, decal transfer, monolithic microwave integrated circuit (MMIC) technology, chemistry See etching techniques, or other suitable technique. For example, according to the chemical etching technique, the dielectric layer may be cladding on one of the conductive materials described above. The conductive material may then be selectively etched away from the dielectric layer using conventional chemical etching techniques to form any of the microstrip patterns described herein. Where applicable, the second dielectric layer is bonded to the aforementioned dielectric surface with a conductive material using any suitable technique, such as forming a bond with a very thin (eg 1.5 mil) thermal bonding film. Can be.

He was also published in 1998 as a "double-layer microstrip antenna" by Hsieh as a doctoral dissertation at the Faculty of Electrical Engineering, Southern Methodist University, and published in Antenna and Propagation in August 1995. Moments discussed in a paper titled "Planar Dual-Band Microstrip Antennas" by CS Lee, V. Nalbandian, and F. Schwering, published in an IEEE transaction. See the following description of the present invention for using calculations and analysis such as methods and joint models. All of these papers are incorporated herein by reference, together together referred to as "Lee and Hsieh".

Medium-gain antenna (for base station antenna) Application example

1 To  3

1 and 2, reference numeral 100 generally denotes a planar microstrip array antenna implementing the features of the present invention for transmitting and receiving beams. Antenna 100 preferably includes a dielectric layer 112 that is generally square. The width 102 and length 102 of the layer 112 are determined by the spacing and number of patches used as described below, and preferably a width of at least 0.50λ _ε beyond the outer edges of the patches 120. And length 102a.

As most clearly shown in FIG. 2, the dielectric layer 112 has a bottom surface 112a to which the conductive ground plane 116 is bonded, an arrangement of the central radiation patch 122 and the conductive radiation patch 120. Top surfaces 112b are joined between the 120, 122, striplines 124, and ground plane 116 to form a radial cavity in the dielectric 112. Referring back to FIG. 1, the patches 120, 122 generally have four corners 120a and four radiating edges 120b, respectively, with each edge preferably having a length 120c of about 0.50λ _ε . It is a square shape having. Patches 120 and 122 are electrically interconnected to an array of conductive striplines 124 that are substantially parallel through one edge 120a or two diagonally opposite edges 120a. Four tuning stubs 126 extend perpendicularly from the two striplines 124. The patches 120, 122 are preferably spaced by a center-to-center distance 160 of about 1.0λ _ε . The patches 120, 122 are preferably illustrated in FIG. 1 as a square arrangement with five rows and columns of patches 120, 122 for a total of 25 patches 120, 122 constituting the antenna 100. Preferably in an array of squares on top 112b having the same number of columns and rows of patches 120,122. The width 184 of each stripline 124 and the width and length of each stub 126 are preferably determined assuming a characteristic impedance of about 50-200 ohms. A shortening pin 178 is preferably disposed on the antenna 100 to electrically connect the ground plane 116 to the central patch 122 to suppress unwanted mode excitation. In order to further suppress unwanted mode excitation, additional shorting pins (not shown) connecting ground plane 116 to patches 120 may also be disposed in antenna 100. Alternatively, in some examples, it may be desirable to omit one or all shorting pins 178 from the antenna 100.

Dimensions of patches 120, 122, striplines 124, stubs 126, openings 150, and center-to-center spacing 160 for optimal performance at a particular frequency Are calculated separately so that high standing waves are generated in the antenna cavity formed in the dielectric 122, and the fields radiated from the radiating edges 120b constitutively interfere with each other to achieve desired antenna characteristics such as high directivity. Serve The number of patches 120, 122 not only determines the total size, but also the directivity of the antenna 100. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the size and location of each patch 120, 122 and the feeding scheme. In order to obtain high directivity, the field distribution between the radiating members is as uniform as possible. The calculations and analyzes described above use techniques such as, for example, the co-model method and the moment method discussed by Lee and Shi, and therefore are not discussed in more detail herein.

A conventional SMA (SubMiniature Type A) probe 170 is provided for transmitting or receiving a beam. To transfer EM energy from and / or to the antenna 100, each SMA probe 170 is connected to an outer conductor 172 electrically connected to a ground plane 116 and to a central patch 122. An inner conductor 174. The probe 170 is disposed along the diagonal of the patch 122 near the stripline 124 to optimize the impedance matching of the antenna 100. Although the probe 170 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) can be used to bond and maintain contact between the inner conductor 174 and the central patch 122, and the connection when the SMA probe 170 penetrates the ground plane 116. Appropriate seals (not shown) may be provided to seal the airtight seal. The other end of the SMA probe 170, which is not connected to the antenna 100, may be connected via a cable (not shown) to a signal generator or to a receiver such as a satellite signal decoder used for television signals.

In operation, antenna 100 may be used to transmit and receive linearly polarized wave (LP) EM beams. To illustrate how the antenna 100 can be used to receive a beam, the antenna 100 is placed in a residential area and receives a beam from a stationary or equatorial satellite that carries a television signal within a predetermined frequency band or channel. Can be oriented to The antenna 100 is so oriented by orienting the top surface 112b toward the source of the beam so that it is generally perpendicular to the direction of the beam. Assuming the members of the antenna 100 have the correct size to receive the beam, the beam passes through the openings 150 and induces standing waves, which resonate within the dielectric layer 112. The standing wave induced in the resonant cavity formed by the dielectric layer 112 communicates through the SMA probe 170 to a receiver such as a decoder (not shown). It is known that antennas transmit and receive signals reciprocally. Therefore, it can be seen that the operation of the antenna 100 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Therefore, the transmission of the signal by the antenna 100 is not described further herein.

The invention can take many forms and examples. The embodiments described with reference to FIGS. 1 and 2 are intended to illustrate, not limit, the invention. Accordingly, several modifications may be made without departing from the spirit and scope of the invention. For example, additional patches 120 may be provided to narrow the beam, or fewer patches 120 may be used to reduce the physical space needed for the antenna 100 of the present invention. 1 and 2 may be configured in a triangular structure used in a communication cell (telecom cell). The stubs 126 may be reconfigured to form other embodiments, one of which is illustrated and discussed in more detail below with respect to FIG. 3.

3 illustrates details of a single mode antenna 300 according to another embodiment of the present invention. Since the antenna 300 includes many of the same members as the members of the antenna 100, these members are denoted by the same reference numerals and will not be described in further detail. According to the embodiment of FIG. 3, in contrast to the embodiment of FIG. 1, four stubs 126 are replaced by two stubs 326 along a line extending diagonally across the central patch 122. Extend outward. Otherwise, the operation of the antenna 300 illustrated in FIG. 3 is substantially similar to the operation of the antenna 100 illustrated in FIG. 1.

4 To  7

4 and 5, reference numeral 400 generally denotes a planar microstrip array antenna that implements features of the present invention for dual-mode operation, such as transmitting and receiving EM beams. Antenna 400 preferably comprises a generally square dielectric layer 412. The width 402 and the length 402 of the layer 412 are determined by the number of patches used below, preferably the width and length 402a of at least 0.50λ _ε over the outer edges of the patches 420. Extend by.

As most clearly shown in FIG. 5, dielectric layer 412 has a bottom surface 412a to which conductive ground surface 416 is bonded, patches 420 and 422, stripline 424 and ground surface 416. An upper surface 412b to which the arrangement of the central radiation patch 422 and the conductive radiation patch 420 are joined is formed to form a resonant cavity in the dielectric layer 412. Referring back to FIG. 4, patches 420 and 422 are generally square, each having four corners 420a and four radiating edges 420b, each having a length 420c of about 0.50λ _ε . As seen in FIG. 4, the patches 420, 422 are horizontally conductive stripline (substantially parallel to the arrangement of the substantially parallel vertical conductive stripline 426 bonded to the dielectric layer 412 through the edges 420a. 424 is electrically interconnected. Four tuning stubs 428 extend diagonally outward from the horizontal stripline 424 and the vertical stripline 426 and from the edges 420a of the central patch 422, and are also bonded to the dielectric layer 412. The patches 420 and 422 are preferably spaced by a center-to-center distance slightly less than 1.0λ _ε . The patches 420, 422 are the same, illustrated in FIG. 4 as a square arrangement with five rows and five columns of patches 420, 422 for a total of 25 patches 420, 422 constituting the antenna 400. It is arranged in a square arrangement on the top surface 412b with patches 420 and 422 of an odd number of columns and rows (spring at 45 ° angle to the horizontal line in FIG. 4). The width 484 of each stripline 424, 426 (FIG. 4) and the width of each stub 428 are preferably determined assuming a characteristic impedance of about 50 to 200 ohms. Shorting pin 478 is preferably disposed on antenna 400 to electrically connect ground plane 416 to central patch 422 to suppress unwanted mode excitation. Additional shorting pins (not shown) may also be disposed in antenna 400 to couple ground plane 416 to patches 420 to further suppress unwanted mode excitation. Alternatively, in some examples, it may be desirable to omit one or all shorting pins 478 from the antenna 400.

For optimal performance at a particular frequency, patches 420 and 422, striplines 424 and 426, stubs 428, openings 450, and center-to-center spacing 460 The dimensions of are calculated separately so that high standing waves are generated in the antenna cavity formed in the dielectric 412, and the fields radiated from the radiating edges 420b constitutively interfere with each other.

The number of patches 420, 422 not only determines the total size of the antenna 400, but also the directivity. The side lobe level of the antenna 400 is determined by the field distribution between the radiating members 420. Therefore, antenna characteristics, such as topography and side lobe levels, are controlled by the size and location of each patch 420 and 422 and by the manner of feeding. In order to achieve high directivity, the field distribution between the radiating members 420 is as uniform as possible. There are null points at the connecting striplines 424 and 426 and the dielectric layer 412 in the patches 420 and 422. The calculations and analyzes described above are for example the moment method described above in the software Ensemble ^™ available from Ansoft Corp., Pittsburgh, Pennsylvania, and the joint model described above, for example by Lee and Shi. Techniques such as, and therefore are not described in more detail herein.

Preferably, two conventional SMA probes 470 are provided for dual mode operation such as transmitting or receiving beams. Each SMA probe 470 has an outer conductor 472 electrically connected to the ground plane 416 and an inner electrically connected to the central patch 422 to transfer EM energy from and / or to the antenna 400. (Or supply) conductor 474. The probe 470 is placed along the diagonal of the patch 422 near the striplines 424 and 426 to optimize impedance matching of the antenna 400 and to reduce crosstalk and cross-polarization. do. Although the probe 470 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to bond and maintain contact between the inner conductor 474 and the central patch 422, and the connection when the SMA probe 470 penetrates the ground plane 416. Appropriate seals (not shown) may be provided to hermetically seal the seals. The other end of the SMA probe 470, which is not connected to the antenna 400, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 400 may be used to transmit or receive linearly polarized wave (LP) EM beams. To illustrate how antenna 400 can be used to receive beams, antenna 400 is arranged in a residential home and carries beams from stationary or equatorial satellites that carry television signals within a predetermined frequency band or channel. Can be directed to receive. Antenna 400 is directed by orienting top surface 412b toward the beam source, and is generally perpendicular to the direction of the beam. Assuming the members of the antenna 400 have the correct size to receive the beam, the beam penetrates through the openings 450 to induce standing waves, which resonate within the dielectric layer 412. The standing waves induced in the resonant cavities formed by the dielectric layer 412 are communicated through the SMA probe 470 to a receiver such as a decoder (not shown).

In antenna 400, vertical modal excitation is perpendicular to the horizontal mode so that crosstalk between two input signals is minimized. In other words, two orthogonal vertical and horizontal modes can be excited independently.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 400 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Therefore, the transmission of the signal by the antenna 400 is not described further herein.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 4 and 5 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 420 may be provided to narrow the beam, or fewer patches 420 may be used to reduce the physical space needed for the antenna 400 of the present invention. An embodiment using fewer patches is illustrated in FIGS. 6 and 7 by antenna 600. In another example, one of the two SMA probes 470 may be removed (or not attached) for single-mode operation of transmitting or receiving an EM beam. Antenna 400 may be used to receive and / or transmit circularly polarized wave (CP) EM beams. In some examples, it may be desirable to omit the shorting pins 478 from the antenna 400.

8 and 9

8 and 9, reference numeral 800 generally denotes a planar microstrip array antenna that implements features of the present invention for dual-mode operation such as transmitting and / or receiving EM beams. Antenna 800 preferably includes a dielectric layer 812 that is generally square. The width 802 and the length 802 of the layer 812 are determined by the number of patches 820 used below, and preferably the width and length of at least 0.50λ _ε beyond the outer edges of the patch 820. Extend 802a.

As most clearly shown in FIG. 9, the dielectric layer 812 has a bottom surface 812a to which the conductive ground plane 816 is bonded, an arrangement of four central radiating patches 822 and conductive radiating patches 820. A top surface 812b is formed between ground plane 816, striplines 824 and 826, and patches 820 and 822, which are joined to form a resonant cavity in dielectric layer 812. Referring again to FIG. 8, patches 820 and 822 are generally square, each having four corners 820a and four radiating edges 820b, each having a length 820c of about 0.50λ _ε . As seen in FIG. 8, the patches 820, 822 are through the edges 820a, a horizontal conductive stripline substantially parallel to the arrangement of the substantially parallel vertical conductive stripline 826 bonded to the dielectric layer 812. Electrically interconnected to an array of 824. Tuning stub 828 extends diagonally outward from the edge 820a of each central patch 822 and towards the center of the antenna 800. The stubs 828 are also bonded to the dielectric layer 812. The patches 820, 822 are preferably spaced apart by a center-to-center distance 860 slightly less than 1.0λ _ε . Patches 820 and 822 are square arrays with four rows and four columns of patches 820 and 822 for a total of 16 patches 820 and 822 constituting antenna 800, as illustrated in FIG. It is arranged in a square arrangement on top surface 812b with patches 820 and 822 of even number of columns and rows (horizontal in FIG. 8 when viewed at 45 ° angle). The width 884 of each stripline 824, 826 (FIG. 8) and the width and length of each stub 828 are preferably determined assuming a characteristic impedance of about 50-200 ohms. Shorting pin 878 is preferably disposed on antenna 800 to electrically connect ground plane 816 to each central patch 822 to suppress unwanted mode excitation. Additional shorting pins (not shown) may be disposed in antenna 800 to connect ground plane 816 to patches 820 to further suppress unwanted mode excitation. Alternatively, in some examples, it may be desirable to omit one or all shorting pins 878 from the antenna 800.

For optimal performance at a particular frequency, patches 820, 822, striplines 824, 826, stubs 828, openings 850, and center-to-center spacing 860 The dimensions of are calculated separately so that high standing standing waves are generated in the antenna cavity formed in the dielectric 812, and the fields radiated from the radiating edges 820b constitutively interfere with each other.

The number of patches 820, 822 not only determines the total size, but also the directivity of the antenna 800. The sublobe levels of the antenna 800 are determined by the field distribution between the radiating members 820, 822. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the size and location of each patch 820, 822 and by the manner of supply. To obtain high directivity, the field distribution between the radiating members 820, 822 is as uniform as possible. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

Preferably, two conventional SMA probes 870 are provided for dual mode operation such as transmitting or receiving beams. Each SMA probe 870 has an outer conductor 872 electrically connected to the ground plane 816 and an inner electrically connected to the central patch 822 for delivering EM energy to and / or from the antenna 800. (Or supply) conductor 874. Thus, two probes 870 are connected to two selected adjacent central patches 822. The probe 870 follows the diagonal of each of the two selected central patches 822 near striplines 824 and 826 to optimize impedance matching of the antenna 800 and to reduce crosstalk and cross polarization. Is placed. Although the probe 870 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to bond and maintain contact between the inner conductor 874 and the central patch 822, and the connection when the SMA probe 870 penetrates the ground plane 816. Appropriate seals (not shown) may be provided to hermetically seal the seals. The other end of the SMA probe 870, which is not connected to the antenna 800, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 800 may be used to transmit or receive linearly polarized wave (LP) EM beams. To illustrate how the antenna 800 can be used to receive beams, the antenna 800 receives beams from stationary or equatorial satellites that are located in the residential home and carry television signals within a predetermined frequency band or channel. Can be directed to. Antenna 800 is directed orienting top surface 812b toward the beam source and is generally perpendicular to the direction of the beam. Assuming the members of the antenna 800 have the correct size to receive the beam, the beam penetrates through the openings 850 to induce standing waves, which resonate within the dielectric layer 812. The standing waves induced in the resonant cavities formed in the dielectric layer 812 are communicated through a SMA probe 870 to a receiver such as a decoder (not shown).

In antenna 800, vertical mode excitation is perpendicular to the horizontal mode so that crosstalk between two input signals can be minimized. In other words, two orthogonal vertical and horizontal modes can be excited independently.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of antenna 800 for transmitting signals is the same as the operation of antennas for receiving signals. Therefore, the transmission of the signal by the antenna 800 is not described further herein.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 8 and 9 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 820 may be provided to narrow the beam, or fewer patches 820 may be used to reduce the physical space needed for the antenna 800 of the present invention. In another example, one of the two SMA probes 870 may be removed (or not attached) for single-mode operation of transmitting or receiving an EM beam. Antenna 800 may be used to receive and / or transmit circularly polarized wave (CP) EM beams.

10 To  12

10-12, reference numeral 1000 generally denotes a planar microstrip array antenna that implements features of the present invention for dual-mode operation, such as transmitting and / or receiving EM beams. Antenna 1000 preferably includes first and second dielectric layers 1012 and 1014 that are generally square. The width 1002 and the length 1002 of the layers 1012 and 1014 are determined by the number of patches 1020 and 1022 used below, preferably at least 0.50λ _ε beyond the outer edges of the patch 1020. Extends by the width and length 1002a.

As most clearly shown in FIG. 11, dielectric layer 1012 has a bottom surface 1012a to which conductive ground plane 1016 is bonded, an arrangement of four central radiation patches 1022 and conductive radiation patches 1020. A top surface 1012b is formed between ground plane 1016, striplines 1024, 1026, and patches 1020, 1022 to form a resonant cavity in dielectric layer 1012. The second dielectric layer 1014 is bonded to the top surface 1012b of the dielectric layer 1012 so that patches 1020 and 1022 are interposed between the dielectric layers 1012 and 1014.

As most clearly shown in FIG. 12, patches 1020 and 1022 are generally square, each having four corners 1020a and four radiating edges 1020b, each having a length 1020c of about 0.50λ _ε Has As seen in FIG. 12, the patches 1020 and 1022 are horizontally substantially parallel to the arrangement of the substantially parallel vertical conductive stripline 1026 interposed between the dielectric layers 1012 and 1014 through the edges 1020a. Is electrically interconnected to an array of conductive striplines 1024. A stub 1025 interposed between the dielectric layers 1012, 1014 extends over each stripline 1024, 1026 from the edge 1020a of each patch 1020, 1022. A stripline 1027 interposed between dielectric layers 1012 and 1014 electrically connects each stub 1025 to the two nearest stubs 1025. A tuning stub 1028 interposed between the dielectric layers 1012, 1014 extends outwardly toward the center of the antenna 1000 for impedance matching from one stub 1025 of each central patch 1022.

The patches 1020 and 1022 are preferably spaced apart by a center-to-center distance 1060 that is slightly less than 1.0λ _ε . The patches 1020, 1022 are preferably illustrated in FIG. 12 as a square arrangement with four rows and four columns of patches 1020, 1022 for a total of 16 patches 1020, 1022 constituting the antenna 1000. Are arranged in a square arrangement on top surface 1012b having patches 1020 and 1022 of the same even number of columns and rows (horizontal in FIG. 10 when viewed at an angle of 45 °). The width 1084 (FIG. 10) of each stripline 1024, 1026, and the width and length of each stub 1025, 1028 are preferably determined assuming a characteristic impedance of about 50-200 ohms. Shorting pins (not shown) are optionally disposed on antenna 1000 to electrically connect ground plane 1016 to one or more patches 1020 and / or 1022 to suppress unwanted mode excitation. Using a stub such as 1025 in the illustrated planar antennas provides impedance matching.

For optimal performance at a particular frequency, patches 1020 and 1022, striplines 1024, 1026 and 1027, stubs 1025 and 1028, openings 1050 and center-to-center The dimensions of the spacing 1060 are calculated separately so that high standing standing waves are generated in the antenna cavity formed in the dielectric 1012, and the fields radiated from the radiating edges 1020b constitutively interfere with each other. The number of patches 1020, 1022 determines the directivity as well as the total size of the antenna 1000. The sublobe levels of the antenna 1000 are determined by the field distribution between the radiating members 1020 and 1022. Therefore, antenna characteristics such as directivity and side lobe levels are controlled by the size and position of each patch 1020 and 1022 and by the manner of supply. In order to obtain high directivity, the field distribution between the radiating members 1020 and 1022 is as uniform as possible. There are points at the connecting striplines 1024, 1026 and the dielectric layers 1012, 1014 in the patches 1020, 1022 where there is no electric field. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

Preferably, two conventional SMA probes 1070 are provided for dual mode operation such as transmitting or receiving beams. As most clearly shown in FIG. 11, each SMA probe 1070 includes an external conductor 1072 electrically connected to the ground plane 1016 for transferring EM energy from and / or to the antenna 1000; It includes an inner (or supply) conductor 1074 extending through a hole formed in two central patches 1022 and a ground plane 1016 and electrically connected to the patch 1023. The patch 1023 is preferably square and its sides have a length of about 2 mm to about 5 mm, typically about 2.5 mm to about 4.5 mm, preferably about 3 mm. Thus, two SMA probes 1070 are connected to two selected adjacent central patches 1022. Probe 1070 is placed along the diagonal of each of the two selected central patches 1022 close to striplines 1024 and 1026 to optimize impedance matching of antenna 1000, reducing crosstalk and cross polarization. . Although the probe 1070 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to bond and maintain contact between the inner conductor 1074 and the selected central patch 1022, with the SMA probe 1070 penetrating the ground plane 1016. In this case, an appropriate seal (not shown) may be provided to hermetically seal the connection. The other end of the SMA probe 1070 not connected to the antenna 1000 is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 1000 may be used to transmit or receive linearly polarized wave (LP) EM beams. To illustrate how the antenna 1000 can be used to receive beams, the antenna 1000 receives beams from stationary or equatorial satellites that are located in a residential house and carry television signals within a predetermined frequency band or channel. Can be directed to. Antenna 1000 is directed orienting top surface 1012b toward the beam source and is generally perpendicular to the direction of the beam. Assuming the members of the antenna 1000 have the correct size to receive the beam, the beam penetrates through the opening 1050 (FIG. 11) to induce standing waves, which resonate within the dielectric layer 1012. Standing waves induced in the resonant cavities formed in the dielectric layer 1012 are communicated through a SMA probe 1070 to a receiver such as a decoder (not shown).

In antenna 1000, vertical mode excitation is perpendicular to the horizontal mode so that crosstalk between two input signals can be minimized. In other words, two orthogonal vertical and horizontal modes can be excited independently.

It is known that antennas transmit and receive signals to each other. Therefore, it will be understood that the operation of the antenna 1000 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Therefore, the transmission of the signal by the antenna 1000 is not described further herein.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 10-12 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 1020 may be provided to narrow the beam, or fewer patches 1020 may be used to reduce the physical space required for the antenna 1000 of the present invention. In another example, one of the two SMA probes 1070 may be removed (or not attached) for single-mode operation of transmitting or receiving an EM beam. Antenna 1000 may be used to receive and / or transmit circularly polarized wave (CP) EM beams.

13 to 15

13-15, reference numeral 1300 generally denotes a planar microstrip array antenna that implements features of the present invention for dual-mode operation, such as transmitting and / or receiving EM beams. Antenna 1300 preferably includes first and second dielectric layers 1312 and 1314 that are generally square. The width 1302 and the length 1302 of the layers 1312 and 1314 are determined by the number of patches 1320 and 1322 used below, preferably at least 0.50λ _ε beyond the outer edges of the patch 1320. Extends by a width and a length 1302a.

As most clearly shown in FIG. 14, dielectric layer 1312 has a bottom surface 1312a to which conductive ground surface 1316 is bonded, preferably twelve outer radiation patches 1320 (FIG. 13) and eight intermediates. An array of radiation patches 1321 and four internal radiation patches 1322 creates a resonant cavity in dielectric layer 1312 between ground plane 1316, striplines 1324, 1352, and patches 1320, 1321, 1322. An upper surface 1312b joined to form is formed. The second dielectric layer 1314 is bonded to the top surface 1312b of the dielectric layer 1312 so that patches 1320, 1321, 1322 are interposed between the dielectric layers 1312, 1314.

As most clearly shown in FIG. 15, patches 1320, 1321, and 1322 are generally square, each having four corners 1320a and four radiating edges 1320b, each about 0.50λ _ε in length ( 1320c). As seen in FIG. 15, patches 1320, 1321, and 1322 are vertical and horizontal (as seen in FIGS. 13 and 15) conductive stripline interposed between dielectric layers 1312 and 1314 through edges 1320a. Are electrically interconnected through the arrangement of 1324. An interpatch area 1352 is formed in each area surrounded by stripline 1324 and not including patches 1320, 1321, 1322. A stub 1325 interposed between dielectric layers 1312, 1314, adjacent to inter-patch region 1352, bonded by one or more inner patches 1322, each of each patch 1320, 1321, 1322. It extends from each edge 1320a over each stripline 1324. A stripline 1326 interposed between the dielectric layers 1312 and 1314 electrically connects each stub 1325 to the two nearest stubs 1325. Tuning stubs 1328 interposed between dielectric layers 1312 and 1314 are each adjacent adjacent inter-patch regions 1352 bounded by two intermediate patches 1321 and two internal patches 1322 for impedance matching. It extends from each stub 1325 of patches 1321 and 1322.

The patches 1320, 1321, 1322 are spaced apart by a center-to-center distance 1360 which is preferably about 1.0λ _ε . The patches 1320, 1321, 1322 are arranged in a square arrangement on the top surface 1312b having the same even number of columns and rows of patches 1320, 1321, 1322. The width 1342 (FIG. 13) of each stripline 1324, 1326, and the width and length of each stub 1325, 1328 are preferably determined assuming a characteristic impedance of about 50-200 ohms. Shorting pins (not shown) are optionally disposed on antenna 1300 to electrically connect ground plane 1316 to one or more patches 1320, 1321, and / or 1322 to suppress unwanted mode excitation.

Patches 1320, 1321, 1322, striplines 1324, 1326, stubs 1325, 1328, openings 1350, region 1352, and the like to achieve optimal performance at a particular frequency. The dimensions of the center-to-center spacing 1360 are individually calculated such that high standing standing waves are generated in the antenna cavity formed in the dielectric 1312 and the fields radiated from the radiating edges 1320b constitutively interfere with each other. do. The number of patches 1320, 1321, 1322 not only determines the total size, but also the directivity of the antenna 1300. The sublobe levels of the antenna 1300 are determined by the field distribution between the radiating members 1320, 1321, 1322. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the size and location of each patch 1320, 1321, 1322, and the manner of supply. To obtain high directivity, the field distribution between the radiating members 1320, 1321, 1322 is as uniform as possible. There are points in the dielectric layer 1312 between the striplines 1324, 1326 and the patches 1320, 1321, 1322 that connect to the ground plane 1316 without an electric field. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

Preferably, two conventional SMA probes 1370 are provided for dual mode operation such as transmitting or receiving beams. As most clearly shown in FIG. 14, each SMA probe 1370 is coupled with an external conductor 1372 electrically connected to a ground plane 1316 to transfer EM energy from and / or to the antenna 1300. And an inner (or supply) conductor 1374 extending through the holes formed in the two inner patches 1322 and ground plane 1316 and electrically connected to the patch 1323. The patch 1323 is preferably square and the sides have a length of about 2 mm to about 5 mm, typically about 2.5 mm to about 4.5 mm, preferably about 3 mm. Thus, two SMA probes 1370 are connected to two adjacent central patches 1322. The probe 1370 is disposed along the diagonal of each of the two selected central patches 1322 close to the stripline 1324 to optimize the impedance matching of the antenna 1300 and reduce crosstalk and cross polarization. Although the probe 1370 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to maintain bonding and contact between the inner conductor 1374 and the selected central patch 1322, and the SMA probe 1370 may be connected to the ground plane 1316. Appropriate seals (not shown) may be provided to hermetically seal the connections when penetrating. The other end of the SMA probe 1370, which is not connected to the antenna 1300, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 1300 may be used to transmit or receive linearly polarized wave (LP) EM beams. To illustrate how the antenna 1300 can be used to receive beams, the antenna 1300 receives beams from stationary or equatorial satellites that are located in a residential house and carry television signals within a predetermined frequency band or channel. Can be directed to. Antenna 1300 is directed orienting top surface 1312b towards the beam source and is generally perpendicular to the direction of the beam. Assuming the members of the antenna 1300 have the correct size to receive the beam, the beam penetrates through the openings 1350 and the regions 1352 to induce standing waves, which resonate within the dielectric layer 1312. The standing wave induced in the resonant cavity formed by the dielectric layer 1312 is communicated through a SMA probe 1370 to a receiver such as a decoder (not shown).

In the antenna 1300, the vertical mode excitation is perpendicular to the horizontal mode so that crosstalk between two input signals can be minimized. In other words, two orthogonal vertical and horizontal modes can be excited independently.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 1300 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Therefore, the transmission of the signal by the antenna 1300 is not described further herein.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 13-15 are intended to illustrate, not limit, the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 1320 may be provided to narrow the beam, or fewer patches 1320 may be used to reduce the physical space needed for the antenna 1300 of the present invention. In another example, one of the two SMA probes 1370 may be removed (or not attached) for single-mode operation of transmitting or receiving an EM beam. The antenna 1300 may be used to receive and / or transmit circularly polarized wave (CP) EM beams.

Figure 16 To  18

16-18, reference numerals 1600 and 1800 generally denote linear microstrip array antennas that implement features of the present invention for dual-mode operation, such as transmitting and / or receiving EM beams. The linear array antenna 1600 is configured to produce narrow beams in the array direction, but wide beams in the direction perpendicular to the array. Antenna 1600 preferably includes a generally rectangular dielectric layer 1612. The length 1602 of the layer 1612 is determined by the number of patches 1620 used below, preferably a width 1604a and a length 1602a of at least 0.50λ _ε over the outer edges of the patch 1620. )

As most clearly shown in FIG. 17, dielectric layer 1612 includes bottom surface 1612a to which conductive ground surface 1616 is bonded, conductive radiation patches 1620 (FIG. 16) and central radiation patches 1622. The arrangement forms a top surface 1612b that is joined between ground plane 1616, striplines 1620, patches 1620, 1622 to form a resonant cavity in dielectric layer 1612. (It should be noted that the ground plane 1616 of Figure 17 should cover the entire area of the bottom face of the dielectric slab.)

Referring back to FIG. 16, patches 1620 and 1622 are generally square, each having four corners 1620a and four radiating edges 1620b, each having a length 1620c of about 0.50λ _ε . As seen in FIG. 16, patches 1620 and 1622 are electrically interconnected through edges 1620a and crossed conductive striplines 1624 joined to dielectric layer 1612. Two tuning stubs 1628 extend diagonally outward from the two edges 1620a of the central patch 1622 and are also bonded to the dielectric layer 1612. The patches 1620 and 1622 are preferably spaced apart by a center-to-center distance 1660 which is slightly less than about 1.0λ _ε . The patches 1620, 1622 are illustrated in FIG. 16 as having two patches 1620 on each side of a single patch 1622 for the total of five patches 1620, 1622 constituting the antenna 1600. , Arranged in a single-column array on top surface 1612b. The width 1684 (FIG. 16) of each stripline 1624 and the width and length of each stub 1628 are preferably determined assuming a characteristic impedance of about 50-200 ohms. Shorting pin 1678 is preferably disposed on antenna 1600 to electrically connect ground plane 1616 to center patch 1622 to suppress unwanted mode excitation. Additional shorting pins (not shown) may also be disposed in antenna 1600 to couple ground plane 1616 to patches 1620 to further suppress unwanted mode excitation. Alternatively, in some examples, it may be desirable to omit one or all shorting pins 1678 from the antenna 1600.

Dimensions of patches 1620, 1622, striplines 1624, stubs 1628, openings 1650, and center-to-center spacing 1660 for optimal performance at a particular frequency. Are calculated separately so that the high standing waves are generated in the antenna cavity formed in the dielectric 1612, and the fields radiated from the radiating edges 1620b constitutively interfere with each other. The number of patches 1620 and 1622 not only determines the total size, but also the directivity of the antenna 1600. The sublobe levels of the antenna 1600 are determined by the field distribution between the radiating members 1620 and 1622. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the size and location of each patch 1620 and 1622 and by the manner of feeding. To obtain high directivity, the field distribution in the radiating members 1620 and 1622 is as uniform as possible. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

Preferably, two conventional SMA probes 1670 are provided for dual mode operation such as transmitting or receiving beams. Each SMA probe 1670 is electrically connected to a central patch 1622 and an external conductor 1672 electrically connected to a ground plane 1616 for transferring EM energy to and / or from the antenna 1600. An inner (or supply) conductor 1674. The probe 1670 is disposed along the diagonal of the patch 1622 close to the stripline 1650 to optimize the impedance matching of the antenna 1600 and reduce crosstalk and cross polarization. Although the probe 1670 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to maintain bonding and contact between the inner conductor 1674 and the central patch 1622, with the SMA probe 1670 penetrating the ground plane 1616. If appropriate, a suitable seal (not shown) may be provided to hermetically seal the connection. The other end of the SMA probe 1670, which is not connected to the antenna 1600, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 1600 may be used to transmit or receive linearly polarized wave (LP) EM beams. Antenna 1600 is directed orienting top surface 1612b towards the beam source and is generally perpendicular to the direction of the beam. Assuming the members of the antenna 1600 have the correct size to receive the beam, the beam penetrates through the openings 1650 to induce standing waves, which resonate within the dielectric layer 1612. The standing wave induced in the resonant cavity formed by the dielectric layer 1612 is communicated through a SMA probe 1670 to a receiver such as a decoder (not shown).

In antenna 1600, vertical mode excitation is perpendicular to the horizontal mode so that crosstalk between two input signals can be minimized. In other words, two orthogonal vertical and horizontal modes can be excited independently.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 1600 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Therefore, the transmission of the signal by the antenna 1600 is not further described herein.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 16-18 are not intended to limit the invention but to illustrate. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 1620 may be provided to narrow the beam, or fewer patches 1620 may be used to reduce the physical space needed for the antenna 1600 of the present invention. Antenna 1600 may be used to receive and / or transmit circularly polarized wave (CP) EM beams. In another example, the outer edges of dielectric layer 1612 may be wrapped in a conductive foil spaced apart from patches 1620 to form edge conductors, reduce surface-mode excitation and increase the gain of the antenna. . In some examples, it may be desirable to omit the shorting pin 1678 from the antenna 1600.

In another variation illustrated in FIG. 18, antenna 1800 may be removed (or not attached) of one of the two SMA probes 1670 and stripline 1624 substantially parallel to the remaining stub 1628. ) And one stub 1628 can be configured for single mode operation of transmitting or receiving an EM beam.

Ultra high gain antenna (such as for direct broadcast satellites) Application example

19 and 20

19 and 20, reference numeral 1900 generally denotes a planar microstrip array antenna that implements features of the present invention for single-mode operation, such as transmitting or receiving a beam. Antenna 1900 includes a dielectric layer 1912 that is generally square. The width 1902 and the length 1903 of the layer 1912 may be the same or different, determined by the number of patches used as described below, and preferably at least over the outer edges of the patch 1920. Extends by a width and length 1902a of 0.50λ _ε .

Dielectric layer 1912 has a bottom surface 1912a to which conductive ground surface 1916 is bonded, and an array of conductive radiation patches 1920 is disposed between patches 1920, striplines 1924, and ground surface 1916. Form a top surface 1912b that is joined to form a resonant cavity in dielectric layer 1912. The patches 1920 are generally square and have four corners 1920a and four radiating edges 1920b, each having a length 1920c of about 0.50λ _ε . As seen in FIG. 19, the patches 1920 are electrically interconnected to an array of parallel vertical conductive striplines 1924 through one of the edges 1920a or two opposite edges 1920a, which in turn Electrically interconnected via horizontal conductive transmission line 1926. Striplines 1924 and transmission line 1926 are bonded to dielectric layer 1912. The patches 1920 are preferably spaced apart by a vertical (as seen in FIG. 19) center-to-center distance 1960 of about 1λ _ε . The patches 1920 are preferably top views, illustrated in FIG. 19 in eight vertical (as seen in FIG. 19) columns 1928 (shown in dashed outlines), offset relative to one another above and below the horizontal transmission line 1926. Disposed in multiple vertical (as seen in FIG. 19) columns on 1912b, each row comprising two patches 1920, making up a total of 32 patches 1920 that make up the antenna 1900. .

The width 1984 of each stripline 1924 is preferably determined assuming a characteristic impedance of about 50 to 200 ohms. Each transmission line 1926 includes a first portion 1926a, a second portion 1926b, and a third portion 1926c. Each first portion 1926a is preferably sized to have a characteristic impedance of about 100 ohms when the input impedance is about 50 ohms. The width and length of each second portion 1926b is controlled by a quarter wavelength converter such that an incoming wave from the supply is substantially transmitted, i.e., the input impedance in the supply line 1974 is properly matched. It is decided. The width and length of each third portion 1926c of the transmission line 1926 is determined such that traveling waves from the supply line 1974 are not reflected at the junctions 1927a and 1927b; Thus, the length of each third portion 1926c is preferably about 1λ _ε to ensure that the difference between the phases of the traveling waves at the junctions 1927a and 1927b is as close to 360 ° as possible. The width of each third portion 1926c is preferably sized such that the characteristic impedance is about one half of the characteristic impedance of the stripline 1924.

For optimal performance at a particular frequency, the dimensions of the patches 1920, striplines 1924, 1926, opening 1950, and center-to-center spacing 1960 are individually calculated so that the high standing standing wave is Fields created in an antenna cavity formed in layer 1912 and radiating from radiating edges 1920b constitutively interfere with each other. The number of patches 1920 determines not only the overall size, but also the directivity of the antenna 1900. The sublobe levels of the antenna 1900 are determined by the field distribution at the radiating edge 1920b. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the location and size and supply of each patch 1920. To obtain high directivity, the field distribution between the radiating members 1920 is as uniform as possible. There are points in the dielectric layer 1912 where there is no electric field. In some examples, one or more shorting pins (not shown) are disposed in the antenna 1900 to electrically connect ground planes, patches, and / or striplines together to suppress unwanted mode excitations. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

A conventional SMA probe 1970 (FIG. 20) is provided for single mode operation such as transmitting or receiving a beam. SMA probe 1970 transmits 1926 between portions 1926a to optimize the appropriate radiation patterns and impedance matching of antenna 1900 to deliver EM energy to and / or from antenna 1900. An inner (or supply) conductor 1974 centrally located and electrically connected along with an outer conductor 1972 electrically connected to a ground plane 1916. Although the probe 1970 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to maintain bonding and contact between the inner conductor 1974 and the central patches 1922, with the SMA probe 1970 penetrating the ground plane 1916. If appropriate, a suitable seal (not shown) may be provided to hermetically seal the connection. The other end of the SMA probe 1970, which is not connected to the antenna 1900, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 1900 may be used to transmit or receive linearly polarized wave (LP) EM beams. Upon transmission of the EM beam, the input signal from the SMA probe 1970 is minimally reflected and the EM into four striplines 1924 and two branches 1926b and 1926c of each branch 1926b and 1926c. Proceed as a traveling wave along transmission line 1926 through first portion 1926a acting as a quarter wave converter for sending power. EM power is transmitted in an array of patches 1920 via striplines 1924. The portions of the patches 1920 and the striplines 1924 then induce high-order standing waves for proper radiation through the apertures 1950 of the antenna 1900.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 1900 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Thus, for example, the antenna 1900 may be arranged to receive a beam from a geostationary or equatorial satellite that is disposed in a residential home and carries a television signal in a predetermined frequency band or channel. The antenna 1900 is directed by orienting the top surface 1912b towards the beam source, and is generally perpendicular to the direction of the beam. Assuming the members of the antenna 1900 have the correct size for receiving the beam, the beam passes through the openings 1950 to induce a high standing standing wave, which resonates within the resonant cavity formed in the dielectric layer 1912 and EM Power is sent to SMA probe 1970 via striplines 1924 and transmission lines 1926. EM power is then transferred from the SMA probe 1970 via a cable (not shown) to a receiver such as a decoder (not shown).

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 19 and 20 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 1920 may be provided to narrow the beam, or fewer patches 1920 may be used to reduce the physical space needed for the antenna 1900 of the present invention.

21 and 22

21 and 22, reference numeral 2100 generally denotes a planar microstrip array antenna that implements features of the present invention for single-mode operation, such as transmitting or receiving a beam. Antenna 2100 includes a dielectric layer 2112 that is generally square. The width 2102 and the length 2103 of the layer 2112 are determined by the number of patches used as described below, preferably at least 0.50 lambda over the outer edges of the patch 2120 and the stripline 2126. extends by the width and length 2102a of _ε .

Dielectric layer 2112 has a bottom surface 2112a to which conductive ground plane 2116 is bonded, and an array of conductive radiation patches 2120 is disposed between patches 2120, striplines 2124, and ground plane 2116. Form a top surface 2112b that is joined to form a resonant cavity in dielectric layer 2112. Patches 2120 are generally square, with four corners 2120a and four radiating edges 2120b, each edge having a length 2120c of about 0.50λ _ε . Patches 2120 are electrically interconnected to one of the arrays of four conductive striplines 2124 through one edge 2120a, which in turn is electrically interconnected through conductive striplines 2126. Striplines 2124 and transmission line 2126 are bonded to dielectric layer 2112. Patches 2120 are preferably spaced by a vertical (as seen in FIG. 21) center-to-center distance 2160 of about 1λ _ε . The patches 2120 are preferably arranged in a number of eight rows on the top surface 2112b, representatively illustrated in FIG. 21 in rows 2114, 2116, each row comprising four patches 2120, There are a total of 32 patches 2120 constituting the antenna 2100. The width of each stripline 2124 is preferably determined assuming a characteristic impedance of about 50 to 200 ohms. Each transmission line 2126 includes a first portion 2126a configured to have a characteristic impedance of about 100 Ohms for an input impedance of about 50 Ohms, as described below with respect to the SMA probe 2170 to ensure proper radiation. As shown, a supply line is disposed in the center of stripline 2126. Each transmission line 2126 further comprises a second portion 2126b, which is preferably configured as a quarter-wavelength transducer with minimal reflection at the junction with the stripline 2126.

For optimal performance at a particular frequency, the dimensions of the patches 2120, striplines 2124, 2126, openings 2150, center-to-center spacing 2160 are individually calculated so that the high standing standing wave is Fields created in the antenna cavity formed in 2112 and radiating from the radiating edges 2120a constructively interfere with each other. The number of patches 2120 not only determines the overall size, but also the directivity of the antenna 2100. The sublobe levels of the antenna 2100 are determined by the field distribution between the radiating members 2120. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the position and size and supply of each patch 2120. To obtain high directivity, the field distribution between the radiating members 2120 is as uniform as possible. There are points where there is no electric field in the dielectric layer 2112 in the connecting stripline 2124 and the patches 2120. In some examples, one or more shorting pins (not shown) are disposed in the antenna 2100 to electrically connect ground planes, patches, and / or striplines together to suppress unwanted mode excitations. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

Conventional SMA probe 2170 (FIG. 22) is provided for single mode operation such as transmitting or receiving beams. Each SMA probe 2170 is adapted to deliver EM energy from and / or to the antenna 2100 to induce centrally-peaked radiation and to optimize the impedance matching of the antenna 2100. An inner (or supply) conductor 2174 centrally located and electrically connected along the transmission line 2126 between the portions 2126a and 2126b and an outer conductor 2172 electrically connected to the ground plane 2116. Although the probe 2170 is preferably an SMA probe, any suitable coaxial probe and / or coupling device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to maintain bonding and contact between the inner conductor 2174 and the central stripline 2126, with the SMA probe 2170 penetrating the ground plane 2116. If appropriate, a suitable seal (not shown) may be provided to hermetically seal the connection. The other end of the SMA probe 2170, which is not connected to the antenna 2100, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 2100 may be used to transmit or receive linearly polarized wave (LP) EM beams. Upon transmission of the EM beam, the second portion 2126b and the first act as a quarter-wavelength converter that sends EM power to the four striplines 2124 with minimal reflection of the incoming signal from the SMA probe 2170. Proceeds as a traveling wave along transmission line 2126 through portion 2126a. EM power is transmitted via the striplines 2124 to the array of patches 2120. The patches 2120 then induce a high standing standing wave for proper radiation through the openings 2150 of the antenna 2100.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 2100 transmitting a signal is the same as the operation of the antenna receiving the signal. Thus, for example, antenna 2100 may be placed in a residential home and directed to receive a beam from a satellite or equatorial satellite that carries a television signal in a predetermined frequency band or channel. Antenna 2100 may be oriented in this manner by orienting top surface 2112b toward the source of the beam such that the top surface is generally perpendicular to the direction of the beam. Assuming the members of the antenna 2100 have the correct size for receiving the beam, the beam passes through the openings 2150 to induce standing waves, which resonate within the dielectric layer 2112. Standing waves induced in the resonant cavity formed in the dielectric layer 2112 are transmitted through striplines 2124 and transmission lines 2126, SMA probe 2170, and delivered to a receiver such as a decoder (not shown). .

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 21 and 22 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 2120 may be provided to narrow the beam, or fewer patches 2120 may be used to reduce the physical space required for the antenna 2100 of the present invention.

Figures 23 and 24

23 and 24, reference numeral 2300 generally denotes a planar microstrip array antenna that implements features of the present invention for dual-mode operation, such as transmitting and receiving beams. Antenna 2300 includes a dielectric layer 2312 that is generally square. The width 2302 and the length 2303 (FIG. 23) of the layer 2312 are determined by the number of patches used as described below, preferably the outer edges of the patch 2320 and the transmission lines 2325 and 2327. ) Extends by a width and a length 2302a of at least 0.50λ _ε .

Dielectric layer 2312 has a bottom surface 2312a to which conductive ground surface 2316 is bonded, and an array of conductive radiation patches 2320 is formed of patches 2320, striplines 2324 and 2326 and ground surface 2316. ) Forms a top surface 2312b that is joined to form a resonant cavity in dielectric layer 2312. Patches 2320 are generally square and have four corners 2320a and four radiating edges 2320b, each edge having a length 2320c of about 0.50λ _ε . As seen in FIG. 23, patches 2320 are electrically interconnected through two adjacent edges 2320a, one of the adjacent edges being electrically connected to one of an array of eight vertical conductive striplines 2324. The other one of the adjacent edges is electrically connected to one of the arrangement of eight horizontal conductive striplines 2326. The vertical striplines 2324 are electrically interconnected through the horizontal conductive transmission line 2325, and the horizontal striplines 2326 are electrically interconnected through the vertical conductive transmission line 2327. Striplines 2324 and 2326 and transmission lines 2325 and 2327 are bonded to dielectric layer 2312. Patches 2320 are preferably spaced by a center-to-center distance 2360 of about 1λ _ε . Patches 2320 are preferably arranged in a number of rows and columns on top surface 2312b, representatively illustrated in FIG. 23, in rows 2328 and columns 2329, each row and column having an antenna 2300. Four patches 2320 are included for a total of 32 patches 2320. The width of each stripline 2324 is preferably determined assuming a characteristic impedance of about 50 to 200 ohms. Each transmission line 2325, 2327 preferably includes a first portion 2325a 2327a configured to have a characteristic impedance of about 100 ohms for an input impedance of about 50 ohms, to ensure proper radiation. As described below with respect to the probe 2370, a supply line is disposed in the center of the stripline 2325. Each transmission line 2325 and 2327 further comprises second portions 2325b and 2327b which are preferably configured as quarter-wavelength transducers with minimal reflection at the junction with the striplines 2324 and 2326. .

For optimal performance at a particular frequency, the dimensions of the patches 2320, striplines 2324 and 2126, openings 2350 and center-to-center spacing 2360 are individually calculated so that the high standing standing wave is separated from the dielectric layer ( Fields created in the antenna cavity formed in 2312 and radiating from the radiating edges 2320b constitutively interfere with each other.

The number of patches 2320 not only determines the overall size, but also the directivity of the antenna 2300. The sublobe levels of the antenna 2300 are determined by the field distribution between the radiating members 2320. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the location and size of each patch 2320 and the manner of supply. To achieve high directivity, the field distribution between the radiating members 2320 is as uniform as possible. There is no electric field in the dielectric layer 2312 on the one hand between ground plane 2316 and on the other hand between patches 2320 and striplines 2324 and 2326. In some examples, one or more shorting pins (not shown) are disposed on the antenna 2300 to electrically connect ground planes, patches, and / or striplines together to suppress unwanted mode excitations. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It is not described in more detail below.

Two conventional SMA probes 2370 (FIG. 24) are provided for dual mode operation such as transmitting or receiving beams. Each SMA probe 2370 follows each transmission line 2325 and 2327 to optimize impedance matching and radiation efficiency of the antenna 2300 to transfer EM energy from and / or to the antenna 2300. An inner (or supply) conductor 2374 centrally located and electrically connected, and an outer conductor 2372 electrically connected to a ground plane 2316. Although the probe 2370 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to bond and maintain contact between each inner conductor 2374 and each transmission line 2325 and 2327, and the SMA probe 2370 may be a ground plane. Appropriate seals (not shown) may be provided to hermetically seal the connections when penetrating 2316. The other end of the SMA probe 2370, which is not connected to the antenna 2300, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 2300 may be used to transmit or receive linearly polarized wave (LP) EM beams. Upon transmission of the EM beam, illustrated as a signal from the SMA probe 2370 to the transmission line 2325, the incoming signal is along the transmission line 2325 through the first portion 2325a and the second portion 2325b. Proceed as a traveling wave, it behaves as a quarter-wave converter that sends EM power to the four striplines 2324 with minimal reflection. EM power is transmitted in an array of patches 2320 via striplines 2324. The patches 2320 then induce a high standing standing wave for proper radiation through the openings 2350 of the antenna 2300.

In the antenna 2300, the vertical mode excitation is perpendicular to the horizontal mode excitation, so that crosstalk between the two input signals is minimized. In other words, two orthogonal vertical and horizontal modes can be excited independently.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 2300 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Thus, for example, antenna 2300 may be placed in a residential home and directed to receive a beam from a satellite or equatorial satellite that carries a television signal in a predetermined frequency band or channel. Antenna 2300 may be so oriented by orienting top surface 2312b towards the source of the beam such that the top surface is generally perpendicular to the direction of the beam. Assuming the members of the antenna 2300 have the correct size to receive the beam, the beam passes through the openings 2350 to induce standing waves, which resonate within the dielectric layer 2312. Standing waves induced in the resonant cavity formed in the dielectric layer 2312 are transmitted to the SMA probe 2370 via stripline 2324 and transmission line 2325 and / or through stripline 2326 and transmission line 2327, and a decoder (not shown). To a receiver such as It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 2300 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Therefore, the operation of antenna 2300 for transmitting signals is not described herein any further.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 23 and 24 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 2320 may be provided to narrow the beam, or fewer patches 2320 may be used to reduce the physical space needed for the antenna 2300 of the present invention. By appropriately modifying near the supply region, a dual-mode operation with two rectangular circular polarizations (CP) can be achieved.

25 and 26

25 and 26, reference numeral 2500 generally denotes a planar microstrip array antenna that implements features of the present invention for single-mode operation, such as transmitting or receiving beams. Antenna 2500 includes a dielectric layer 2512 that is generally square. The width 2502 and the length 2503 of the layer 2512 may or may not be the same and are determined by the number of patches used as described below, and preferably at least 0.50 beyond the outer edges of the patch 2520. extends by the width and length 2502a of λ _ε .

Dielectric layer 2512 has a bottom surface 2512a to which conductive ground surface 2516 is bonded, and an array of conductive radiation patches 2520 is disposed between ground surface 2516, patches 2520, and stripline 2524. Form a top surface 2512b that is joined to form a resonant cavity in dielectric layer 2512. Patches 2520 are generally square and have four corners 2520a and four radiating edges 2520b, each edge having a length 2520c of about 0.50λ _ε . As seen in FIG. 25, patches 2520 are electrically interconnected to an array of substantially parallel vertical conductive striplines 2524 through one edge 2520a or two opposing edges 2520a, which in turn Electrically interconnected through substantially parallel horizontal conductive transmission lines 2526, stripline 2524 and transmission lines 2526 are bonded to dielectric layer 2512. Patches 2520 are preferably spaced by a vertical (as seen in FIG. 25) center-to-center distance 2560 of about 1λ _ε . Patches 2520 are preferably arranged in a number of vertical (as seen in FIG. 25) columns on top surface 2512b, above and below transmission line 2526, typically represented by columns 2528 illustrated by dashed outlines. . The width of each stripline 2524 is preferably determined assuming a characteristic impedance of about 50 to 200 ohms. The transmission line 2526 preferably includes a first portion 2526a configured to have a characteristic impedance of about 100 ohms for an input impedance of about 50 ohms, with respect to the SMA probe 2570 to ensure proper radiation. As will be described later, the supply line is disposed in the center of the transmission line 2526. Transmission line 2526 further includes two second portions 2526b that are configured to be minimally reflected at the junction with stripline 2524.

For optimal performance at a particular frequency, the dimensions of the patches 2520, stripline 2524, opening 2550, center-to-center spacing 2560 are individually calculated so that the high standing standing wave is divided into dielectric layer 2512. Are generated in the antenna cavity, which are formed within, and emanate from the radiating edges 2520b constitutively interfere with each other. The number of patches 2520 not only determines the overall size, but also the directivity of the antenna 2500. The side lobe levels of the antenna 2500 are determined by the field distribution between the radiating members 2520. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the location and size and supply of each patch 2520. To achieve high directivity, the field distribution between the radiating members 2520 is as uniform as possible. There are points in the dielectric layer 2512 near the patches 2520 and striplines 2524 that are free of electric fields. In some examples, one or more shorting pins (not shown) are disposed on the antenna 2500 to electrically connect ground planes, patches, and / or striplines together to suppress unwanted mode excitations. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

A conventional SMA probe 2570 (FIG. 26) is provided for single-mode operation such as transmitting or receiving a beam. Each SMA probe 2570 is centrally located along the transmission line 2526 to optimize the impedance matching and antenna aperture efficiency of the antenna 2500 to transfer EM energy from and / or to the antenna 2500. An inner (or supply) conductor 2574 that is electrically connected, and an outer conductor 2252 that is electrically connected to a ground plane 2516. Although the probe 2570 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to maintain bonding and contact between each inner conductor 2574 and each transmission line 2526, and the SMA probe 2570 may have a ground plane 2516. An appropriate seal (not shown) may be provided to hermetically seal the connection when through. The other end of the SMA probe 2570, which is not connected to the antenna 2500, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 2500 may be used to transmit or receive linearly polarized wave (LP) EM beams. In the transmission of the EM beam, as illustrated using the signal from the SMA probe 2570 to the transmission line 2526, the input signal travels as a traveling wave along the transmission line 2525 through the first portion 2525a and Two branches 2526b then direct EM power to striplines 2524 with minimal reflection. EM power is transmitted via the striplines 2524 to the array of patches 2520. The patches 2520 then induce a high standing standing wave for proper radiation through the openings 2550 of the antenna 2500.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 2500 transmitting a signal is the same as the operation of the antenna receiving the signal. Thus, for example, the antenna 2500 may be placed in a residential home and directed to receive a beam from a satellite or equatorial satellite that carries a television signal in a predetermined frequency band or channel. Antenna 2500 may be so oriented by orienting top surface 2512b toward the source of the beam such that the top surface is generally perpendicular to the direction of the beam. Assuming that the members of the antenna 2500 have the correct size to receive the beam, the beam passes through the openings 2550 to induce standing waves, which is in the resonant cavity of the array of patches 2520 of the dielectric layer 2512. Resonance at Standing waves induced in the resonant cavities formed in the dielectric layer 2512 leak EM power to the SMA probe 2570 via a transmission line network comprising striplines 2524 and 2526 and receive a receiver such as a decoder (not shown). Is delivered to. It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 2500 transmitting a signal is the same as the operation of the antenna receiving the signal. Therefore, the operation of the antenna 2500 for transmitting signals is not described herein any further.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 25 and 26 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 2520 may be provided to narrow the beam, or fewer patches 2520 may be used to reduce the physical space needed for the antenna 2500 of the present invention.

27 and 28

Referring to Figures 27 and 28, reference numeral 2700 generally denotes a planar microstrip array antenna that implements features of the present invention for single-mode operation, such as transmitting or receiving beams. Antenna 2700 includes a dielectric layer 2712 that is generally square. The width 2702 and length 2703 of layer 2712 may or may not be the same and is determined by the number of patches used as described below, preferably at least 0.50 beyond the outer edges of patch 2720. extends by the width and length 2702a of λ _ε .

Referring to FIG. 28, dielectric layer 2712 includes a bottom surface 2712a to which conductive ground surface 2716 is bonded, and an array of conductive radiation patches 2720 (FIG. 27) are ground planes, patches 2720, and strips. Between lines 2724 forms a top surface 2712b that is joined to form a resonant cavity in dielectric layer 2712.

Referring again to FIG. 27, patches 2720 are generally square and have four corners 2720a and four radiating edges 2720b, each edge having a length 2720c of about 0.50λ _ε . As seen in FIG. 27, patches 2720 are electrically interconnected to an array of conductive striplines 2724 that are substantially horizontal and vertical through two, three, or four edges 2720a, which in turn is substantially horizontal. Is electrically interconnected via conductive transmission line 2726. Stripline 2724 and transmission line 2726 are bonded to dielectric layer 2712. The width of each stripline 2724 is preferably determined assuming a characteristic impedance of about 50 to 200 ohms. Transmission line 2726 preferably includes a first portion 2726a configured to have a characteristic impedance of about 100 ohms to an input impedance of about 50 ohms, and supply line 2774 provides an SMA to ensure proper radiation. The probe 2770 is described later and disposed at the center of the transmission line 2726. Transmission line 2726 further includes two second portions 2726b that are configured as quarter-wavelength transducers to minimize reflection. The signal from the second portion 2726b then passes through another quarter-wavelength converter such that the power passing through the vertical transmission line 2724 is evenly distributed to each other.

For optimal performance at a particular frequency, the dimensions of the patches 2720, stripline 2724, opening 2750, center-to-center spacing 2760 are individually calculated so that the high standing standing wave is divided into the dielectric layer 2712. Are generated in the antenna cavity formed within the cavities, and fields radiated from the radiating edges 2720b constitutively interfere with each other.

The number of patches 2720 not only determines the overall size, but also the directivity of the antenna 2700. The sublobe levels of the antenna 2700 are determined by the field distribution at the radiating edges 2720b. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the location and size and supply of each patch 2720. In order to achieve high directivity, the field distribution between the radiating members 2720 is as uniform as possible. There are points in the dielectric layer 2712 near the patches 2720 and striplines 2724 that are free of electric fields. In some examples, one or more shorting pins (not shown) are disposed on the antenna 2700 to electrically connect ground planes, patches, and / or striplines together to suppress unwanted mode excitations. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, It is not described in more detail herein.

A conventional SMA probe 2770 (FIG. 28) is provided for single-mode operation such as transmitting or receiving a beam. Each SMA probe 2770 is a centrally located and electrically connected internal (or supplying) conductor 2774 along the transmission line 2726 for proper radiation to transfer EM energy from and / or to the antenna 2700. And an external conductor 2772 electrically connected to the ground plane 2716. Although the probe 2770 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to maintain bonding and contact between each inner conductor 2774 and the central stripline 2726a, and the SMA probe 2770 may be a ground plane 2716. An appropriate seal (not shown) may be provided to hermetically seal the connection when penetrating. The other end of the SMA probe 2770, which is not connected to the antenna 2700, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 2700 may be used to transmit or receive linearly polarized wave (LP) EM beams. In the transmission of the illustrated EM beam using the signal from the SMA probe 2770 to the transmission line 2726, the incoming signal is first and second portions 2726a and 2726b that act as quarter-wavelength converters. , Then proceed as traveling wave along transmission line 2726 through another quarter-wavelength converter and a power divider to finally deliver the EM power to the striplines 2724. The power distribution is sent to be relatively uniform between the reverberation path and the vertical stripline 2724. EM power is transmitted via the stripline 2724 in an array of patches 2720. The patches 2720 then induce a high standing standing wave for proper radiation through the radiating edges 2720b of each patch 2720 of the antenna 2700.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 2700 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Thus, for example, antenna 2700 may be placed in a residential home and directed to receive a beam from a satellite or equatorial satellite that carries a television signal in a predetermined frequency band or channel. Antenna 2700 may be so oriented by orienting top surface 2712b toward the source of the beam such that the top surface is generally perpendicular to the direction of the beam. Assuming that the members of the antenna 2700 have the correct size for receiving the beam, the beam passes through the openings 2750 to induce standing waves, which is in the resonant cavity of the array of patches 2720 of the dielectric layer 2712. Resonance at The standing wave induced in the resonant cavity formed in the dielectric layer 2712 leaks EM power to the SMA probe 2770 via a transmission line network comprising striplines 2724 and 2726, and a receiver such as a decoder (not shown). Is delivered to. It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 2700 transmitting the signal is the same as the operation of the antenna receiving the signal. Therefore, the transmission of the signal by antenna 2700 is no longer described herein.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 27 and 28 are intended to illustrate, not limit, the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 2720 may be provided to narrow the beam, or fewer patches 2720 may be used to reduce the physical space needed for the antenna 2700 of the present invention.

Figure 29 To  31

29A and 29B (hereinafter "FIG. 29") and FIG. 30, reference numeral 2900 generally refers to a planar microstrip arrangement that implements features of the present invention for dual-mode operation, such as transmitting or receiving beams. Represents an antenna. Antenna 2900 includes a dielectric layer 2912 that is generally square. The width 2902 and the length 2907 of the layer 2912 may or may not be equal and are determined by the number of patches used as described below, preferably at least 0.50 beyond the outer edges of the patch 2920. extends by the width and length 2902a of λ _ε .

Referring to FIG. 30, the dielectric layer 2912 has a bottom surface 2912a to which a conductive ground plane 2916 is bonded, and an array of conductive radiation patches 2920 (FIG. 29) are ground plane 2916 and patch 2920. ), The top surface 2912b is joined between the striplines 2924 to form a resonant cavity in the dielectric layer 2912.

Referring again to FIG. 29, patches 2920 are generally square, having four corners 2920a and four radiating edges 2920b, each edge having a length 2920c of about 0.50λ _ε . As seen in FIG. 29, patches 2920 are electrically interconnected to an array of substantially horizontal and vertical conductive striplines 2924 through two, three, or four edges 2920a, which is a dielectric layer 2912. Is bonded). The striplines 2924 are eventually electrically interconnected through a conductive transmission line 2928 that is substantially perpendicular to a substantially horizontal conductive transmission line 2926. Transmission lines 2926 and 2928 are bonded to dielectric layer 2912 and the intersection of transmission lines 2926 and 2928 is indicated by dashed outlines in FIG. 29 and is described in detail below with respect to FIG. The width of each stripline 2924 is preferably determined assuming a characteristic impedance of about 50 to 200 ohms. Transmission lines 2926 and 2928 preferably include first portions 2926a and 2928a, each configured to have a characteristic impedance of about 100 ohms to an input impedance of about 50 ohms, and to ensure proper radiation. Supply lines 2974 are disposed on respective transmission lines 2926 and 2928 as described below with respect to 2970. Each transmission line 2926, 2928 further comprises two second portions 2926b, 2928b, which are configured as quarter-wavelength transducers to be minimally reflected.

30 illustrates one preferred configuration in which transmission lines 2926 and 2928 can intersect at dashed outline 2927 without electrical contact. Thus, as seen in FIG. 30, the transmission line 2928 includes a bridge that includes two vias 2928c (vias) that pass under the transmission line 2926, and the two biases 2928c It passes through the holes in ground plane 2916 without making electrical contact with ground plane 2916, which is in turn by microstrip 2928d (FIG. 31) electrically isolated from ground plane 2916 through dielectric 2913. Electrically connected. In another embodiment, non-conductive crossing of transmission lines 2926 and 2928 may be made using a directional coupler described below with respect to FIGS. 31 and 32.

For optimal performance at a particular frequency, the dimensions of the patches 2920, transmission lines 2924, 2926, openings 2950, center-to-center spacing 2960 are individually calculated so that the high standing standing wave can Fields created in the antenna cavity formed in 2912 and radiating from the radiating edges 2920b constitutively interfere with each other.

The number of patches 2920 not only determines the overall size, but also the directivity of the antenna 2900. The sublobe levels of the antenna 2900 are determined by the field distribution between the radiating edges 2920b. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the location and size and supply of each patch 2920. In order to achieve high directivity, the field distribution between the radiating members 2920 is as uniform as possible. There are points in the dielectric layer 2912 near patches 2920 and stripline 2924 where there is no electric field. In some examples, one or more shorting pins (not shown) are disposed on the antenna 2900 to electrically connect ground planes, patches, and / or striplines together to suppress unwanted mode excitations. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

Two conventional SMA probes 2970 (FIG. 30) are provided for dual-mode operation such as transmitting and receiving beams. Each SMA probe 2970 is disposed and electrically connected along transmission lines 2926 and 2928 to optimize impedance matching of antenna 2900 to transfer EM energy from and / or to antenna 2900. An inner (or supply) conductor 2974 and an outer conductor 2972 electrically connected to a ground plane 2916. Preferably, the supply lines 2974 are multiples of λ _ε plus about one-quarter wavelength apart from where the transmission lines 2926 and 2928 intersect, as shown in dotted outline 2927 (FIG. 29). Spaced apart by distance 2775. Although the probe 2970 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to maintain bonding and contact between each supply line 2974 and the central stripline 2926a, with the SMA probe 2970 being connected to the ground plane 2916. An appropriate seal (not shown) may be provided to hermetically seal the connection when penetrating. The other end of the SMA probe 2970 not connected to the antenna 2900 is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 2900 may be used to transmit or receive linearly polarized wave (LP) EM beams. In the transmission of an EM beam, illustrated using a signal from SMA probe 2970 to transmission lines 2926, 2928, an incoming signal passes through transmission lines 2926, 2928 through first portions 2926a, 2928a, respectively. Proceeding as a traveling wave, EM power is sent to the two branches 2926b, 2928b and then to the stripline 2924 with minimal reflection. EM power is transmitted via the stripline 2924 to the array of patches 2920. The patches 2920 and portions of stripline 2924 then induce a high standing standing wave for proper radiation through the openings 2950 of the antenna 2900.

In antenna 2900, vertical mode excitation is perpendicular to the horizontal mode so that crosstalk between two input signals is minimized. In other words, two orthogonal vertical and horizontal modes can be excited independently.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of antenna 2900 for transmitting signals is the same as the operation of antennas for receiving signals. Thus, for example, antenna 2900 may be placed in a residential home and directed to receive a beam from a satellite or equatorial satellite that carries a television signal in a predetermined frequency band or channel. Antenna 2900 can be so oriented by orienting top surface 2912b toward the source of the beam such that the top surface is generally perpendicular to the direction of the beam. Assuming that the members of the antenna 2900 have the correct size to receive the beam, the beam passes through the openings 2950 to induce standing waves, which are ground plane 219 and striplines 2924 and patches 2920. Resonates within the resonant cavity in dielectric layer 2912 between the array of. Standing waves induced in the resonant cavities formed in the dielectric layer 2912 leak EM power to the SMA probe 2970 via a transmission line network comprising striplines 2924 and 2926, and receive a receiver such as a decoder (not shown). Is delivered to. It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of antenna 2900 for transmitting signals is the same as the operation of antennas for receiving signals. Therefore, the transmission of the signal by antenna 2900 is no longer described herein.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 29 and 30 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 2920 may be provided to narrow the beam, or fewer patches 2920 may be used to reduce the physical space needed for the antenna 2900 of the present invention. By appropriately modifying the vicinity of the supply region, dual-mode operation with two rectangular circular polarizations (CP) can be achieved.

32 and 33

32 and 33, reference numeral 3200 generally denotes a planar microcrosstrip array antenna that implements features of the present invention for dual-mode operation, such as transmitting or receiving a beam. Antenna 3200 includes a dielectric layer 3212, which is generally square. The width 3202 and the length 3203 (FIG. 32) of layer 3212 may be the same or different and are determined by the number of patches used as described below, preferably the outer edges of patch 3220. Extends beyond the width and length 3202a of at least 0.50λ _ε .

Referring to FIG. 33, the dielectric layer 3212 includes a bottom surface 3212a to which a conductive ground plane 3216 is bonded, and an array of conductive radiation patches 3220 may include a ground plane 3216, patches 3220, and a strip. An upper surface 3212b is formed between the lines 3224 and 3226 to form a resonant cavity in the dielectric layer 3212. Referring to FIG. 32, patches 3220 are generally square, with four corners 3220a and four radiating edges 3220b, each edge having a length 3220c of about 0.5λ _ε . As seen in FIG. 32, patches 3220 are electrically interconnected through an edge 3220a to an array of substantially horizontal conductive striplines 3224 and vertical conductive striplines 3326. The striplines 3224 and 3226 are directional couplers detailed below with respect to FIG. 34 via respective transmission lines 3224a, 3224b, 3226a and 3226b so as to exchange EM energy with the probes detailed with respect to the SMA probe 3270. Electrically interconnected to 3400. Striplines 3224, 3226 and transmission lines 3224a, 3224b, 3226a, 6226b are bonded to dielectric layer 3212. Patches 3220 are preferably spaced by a center-to-center distance 3260 of about 1λ _ε . Patches 3220 are preferably arranged in four sub-arrays and in sub-array 3222 with rows 3328 and columns 329 offset from each other within each sub-array. And is arranged in a number of rows and columns on top surface 3212b, typically represented by dashed outlines. The width of each stripline 3224, 3226 is preferably determined assuming a characteristic impedance of about 50 to 200 ohms. The transmission lines 3224a and 3226a are preferably configured to have a characteristic impedance of about 100 ohms for an input impedance of about 50 ohms, and the supply lines should be properly phased for each stripline and patch for optimum gain. on each stripline 3224, 3226 as described below with respect to the SMA probe 3270 to ensure phase. Transmission lines 3224b and 3226b are preferably configured as two 1 / 4-wavelength transducers in series to minimize reflection.

For optimal performance at a particular frequency, the dimensions of the patches 3220, striplines 3224, 3226, openings 3250, center-to-center spacing 3260, coupler 3100 are calculated separately, A high standing wave is generated in the antenna cavity formed in the dielectric layer 3212, and the fields radiated from the radiating edges 3220b constitutively interfere with each other.

The number of patches 3220 not only determines the overall size, but also the directivity of the antenna 3200. The sublobe levels of the antenna 3200 are determined by the field distribution between the radiating members 3220b. Therefore, antenna characteristics, such as directivity and side lobe levels, are controlled by the location and size of each patch 3220 and by way of feeding. To achieve high directivity, the field distribution between the radiating members 3220 is as uniform as possible. There are points in the dielectric layer 3212 within striplines 3224 and 3226 and patches 3220 where there is no electric field. In some examples, one or more shorting pins (not shown) are disposed in the antenna 3200 to electrically connect ground planes, patches, and / or striplines together to suppress unwanted mode excitations. The calculation and analysis described above uses techniques such as, for example, the moment method described above in the software Ensemble ^™ available from Ansoft Corporation and, for example, the joint model described above by Lee and Shi, and therefore, herein It will not be described in more detail.

Two conventional SMA probes 3270 (only one of which is shown in FIG. 33) are provided for dual-mode operation such as transmitting and receiving beams. Each SMA probe 3270 delivers EM energy from and / or to the antenna 3200 to ensure proper phase for each stripline and patch so that each transmit line 3224a, An inner (or supply) conductor 3274 disposed along and electrically connected along 3226a and an outer conductor 3332 electrically connected to ground plane 3216. Although the probe 3270 is preferably an SMA probe, any suitable coaxial probe and / or connection device may be used to make the connections described above. For example, a conductive adhesive (not shown) may be used to maintain bonding and contact between the inner conductor 3274 and the transmission line 3224a and the SMA probe 3270 penetrating the ground plane 3216. In this case, an appropriate seal (not shown) may be provided to hermetically seal the connection. The other end of the SMA probe 3270, which is not connected to the antenna 3200, is connectable via a cable (not shown) to a receiver such as a signal generator or a satellite signal decoder used for television signals.

In operation, antenna 3200 may be used to transmit and receive linearly polarized wave (LP) EM beams. Upon transmission of the EM beam, illustrated using a signal from SMA probe 3270 with supply line to transmission line 3224a, the incoming signal is sent along the transmission line 3224a via connector 3400 to the opposite transmission line. Proceeds as a traveling wave to 3224a. Transmission line 3224a directs the EM power of the signal to two branches 3224b and then with minimal reflection to stripline 3224 of each branch transmission line 3224b. EM power is transmitted via the striplines 3224 to the array of patches 3220. Subsequently, portions of the patches 3220 and stripline 3224 induce a high standing standing wave for proper radiation through the openings 3250 of the antenna 3200.

Upon transmission of the EM beam, illustrated using a signal from the SMA probe 3270 with supply line to the transmission line 3326a, the incoming signal passes through the connector 3400 along the transmission line 3326a to the opposite transmission line. Proceeds as a traveling wave to 3326a. Transmission line 3326a sends the EM power of the signal to two branch transmission lines 3326b and then with minimal reflection to stripline 3326 of each branch transmission line 3326b. EM power is transmitted via the striplines 3326 to the array of patches 3220. The patches 3220 then induce a high standing standing wave for proper radiation through the openings 3250 of the antenna 3200.

In antenna 3200, vertical mode excitation is perpendicular to the horizontal mode such that crosstalk between two input signals is minimized. In other words, two orthogonal vertical and horizontal modes can be excited independently.

It is known that antennas transmit and receive signals to each other. Therefore, it will be appreciated that the operation of the antenna 3200 for transmitting the signal is the same as the operation of the antenna for receiving the signal. Thus, for example, antenna 3200 may be placed in a residential home and directed to receive a beam from a satellite or equatorial satellite that carries a television signal in a predetermined frequency band or channel. Antenna 3200 may be oriented so as to orient top surface 3212b toward the source of the beam such that the top surface is generally perpendicular to the direction of the beam. Assuming the members of the antenna 3200 have the correct size for receiving the beam, the beam passes through the openings 3250 and induces standing waves that resonate within the dielectric layer 3212. Standing waves induced in the resonant cavity formed in the dielectric layer 3212 leak electromagnetic power through the striplines 3224 and 3226 and the coupler 3400 to the appropriate SMA probe 3270, and with a decoder (not shown). Is delivered to the same receiver.

It will be appreciated that the present invention may take many forms and embodiments. The embodiments described with respect to FIGS. 32 and 33 are intended to illustrate but not limit the invention. Accordingly, several modifications can be made from the above without departing from the spirit and scope of the invention. For example, additional patches 3220 may be provided to narrow the beam, or fewer patches 3220 may be used to reduce the physical space needed for the antenna 3200 of the present invention. By appropriately modifying the vicinity of the supply region, dual-mode operation with two rectangular circular polarizations (CP) can be achieved.

34 and 35

Referring to FIG. 34, reference numeral 3400 is used to couple two EM energy sources to two EM energy destinations such that EM energy can be communicated from two sources / sources to two destinations / destinations without interference. A planar microstrip directional coupler implementing the features of the present invention is shown. As described above with respect to FIGS. 32-33, coupler 3400 is preferably integrated into a microstrip antenna, such as antenna 2900 and antenna 3200. However, coupler 3400 may also function as a standalone coupler, as shown in FIG. 34, and so described herein for simplicity. Thus, coupler 3400 includes a dielectric layer 3412, which is generally square. Dielectric layer 3412 has a width 3402 and a length 3403, which may or may not be the same.

Referring to FIG. 35, dielectric layer 3412 has a bottom surface 3412a to which conductive ground plane 3416 can optionally be joined, and top surface 3412b to which the array of conductive striplines are joined to form a directional coupler. Form. The striplines include first striplines 3420 and 3422 between which EM energy is transferred and second striplines 3424 and 3426 between which EM energy is transferred. The width of each stripline 4124 is preferably determined assuming a characteristic impedance Z ₀ of about 50 to 200 ohms.

Striplines 3420, 3422, 3424, 3426 are substantially square bridges 3430 with two end portions 3432, top and bottom portions 3434, and mid-section portions 3434 as seen in FIG. 34. Is connected to. Preferably, the width of each end portion 3432 is preferably determined assuming a characteristic impedance Z ₀ of about 50 to 200 ohms, and the length 3432a of each end portion 3432 is about 0.25λ _ε to be. Preferably, the width of each upper and lower portion 3434 is determined assuming a characteristic impedance Z ₀ / √2 of about 35 to 141 ohms, and half the length 3434a of each upper and lower portion 3434. ) Is about 0.25λ _ε . Each upper and lower portion 3434 is further characterized by an end 3434b chamfered at an angle of about 45 ° relative to the upper and lower portions. Preferably a mid-portion of the width of the section (3436) is determined assuming a characteristic impedance Z _0/2 of about 25 to 100 ohms.

In operation, when coupler 3400 is used in conjunction with the antenna arrangement of FIG. 29, a line, such as line 2928a illustrated in FIG. 29, is connected to each first stripline 3420, 3422, and in FIG. 29. Lines such as the illustrated line 2926a are connected to each second stripline 3424, 3426. With substantially negligible losses for striplines 3424 and 3426, energy on stripline 2928a is transferred from stripline 3420 to stripline 3422 (or from stripline 3422 to stripline 3420). Similarly, energy on stripline 2926a is transferred from stripline 3424 to stripline 3426 (or from stripline 3426 to stripline 3424) with substantially negligible losses for striplines 3420 and 3422.

Assuming that the dielectric constants of the dielectric layers are substantially equal at the desired frequency, such as at a given frequency, all of the above-described antennas configured for operation at a given frequency are directly proportional to the ratio of the desired frequency to the desired frequency. It will also be appreciated that each dimension of the antenna can be generally scaled and reconfigured for operation at substantially any other desired frequency without significantly changing characteristics such as the antenna's efficiency and radiation pattern.

Although embodiments of the invention have been shown and described, a wide variety of modifications, variations, and substitutions may be considered in the above teachings, and some features of the invention may be used without correspondingly using other features. Accordingly, the appended claims are to be interpreted broadly in a manner consistent with the scope of the present invention, wherein reference numerals provided in parentheses are provided as examples for convenience and efficiency of illustration and in no way limit any claim. Should not be construed as

Claims (50)

A dielectric layer forming a first side and a second side; A conductive ground plane disposed on the first side of the dielectric layer; An array of spaced radiating patches disposed on the second side of the dielectric layer; And An antenna (100-3300) electrically connected to one or more edges of each patch and including one or more striplines disposed on the second side of the dielectric layer. The antenna (100-3300) of claim 1, wherein the patches and striplines are sized and arranged such that a high standing wave is induced in the antenna in response to electromagnetic energy. The antenna (100-3300) of claim 1, wherein the antenna is planar. The antenna of claim 1, further comprising at least one patch for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna and at least one supply means electrically connected to the ground plane. 100-1800). 2. The second conductive element of claim 1, further comprising: a second conductive member electrically connected to at least one patch for extracting electromagnetic energy from the antenna and / or to supply electromagnetic energy to the antenna; Antenna (100-1800) further comprising at least one supply means having a member. The microstripline of claim 1, wherein the microstripline is electrically connected to the ground plane, a line coupled to the opening, and / or one or more patches for extracting electromagnetic energy from the antenna and / or supplying electromagnetic energy to the antenna. An antenna (100-1800) further comprising at least one of an SMA probe and a probe. 2. The apparatus of claim 1, further comprising two or more supply means, each of which comprises a microstripline, a line coupled to the opening, an SMA probe, a probe, each supply means being electronic from the antenna. An antenna (100-1800) electrically connected orthogonally to the ground plane and at least one patch for extracting miracle energy and / or supplying electromagnetic energy to the antenna. The antenna (100-1300) of claim 1, wherein the patches are arranged in a square array of identical rows and columns. 10. The antenna 100 of claim 1, further comprising one or more tuning stubs extending substantially at right angles from at least one of the one or more strip lines and disposed on the second side of the dielectric layer. ). The method of claim 1, wherein the patches comprise four or more patches, Each patch comprises first and second diagonally opposite edges and third and fourth diagonally opposite edges, The striplines are distributed in a proportion between the first group of parallel striplines and the second group of parallel striplines, wherein the striplines of the first group of striplines are substantially in relation to the striplines of the second group of striplines. Oriented at right angles to The first group of striplines are electrically interconnected together at one or more of the first and second diagonally opposite edges of each of two or more of the four or more patches, And said second group of striplines is electrically interconnected together at one or more of said third and fourth diagonally opposing corners of each of at least two of said four or more patches. The method of claim 1, wherein the patches comprise four or more patches, Each patch comprises first and second diagonally opposite edges and third and fourth diagonally opposite edges, The striplines are distributed in a ratio between the first group of parallel striplines and the second group of parallel striplines, wherein the striplines of the first group of striplines are connected to the striplines of the second group of striplines. Oriented substantially perpendicular to, Striplines of the first group are electrically interconnected together at one or more of the first and second diagonally opposing edges of each of two or more of four or more patches, The second group of striplines are electrically interconnected together at one or more of each of the third and fourth diagonally opposite edges of each of two or more of four or more patches, The antenna further comprises one tuning stub extending outward from each corner of the patch. The method of claim 1, wherein the patches comprise four or more patches, each patch comprising first and second diagonally opposite edges and third and fourth diagonally opposite edges, The striplines are distributed in a ratio between the first group of parallel striplines and the second group of parallel striplines, wherein the striplines of the first group of striplines are the stripline of the second group of striplines. Oriented substantially perpendicular to the The first group of striplines are electrically interconnected together at one or more of each of the first and second diagonally opposing corners of each of two or more of four or more patches, The second group of striplines are electrically interconnected together at one or more of each of the third and fourth diagonally opposite edges of each of two or more of four or more patches, The antenna (800) further comprises one tuning stub extending outward from one corner of each of the four patches toward a common point. The method of claim 1, wherein the patches comprise four or more patches, each patch comprising first and second diagonally opposite edges and third and fourth diagonally opposite edges, The striplines are distributed in a ratio between the parallel striplines of the first group and the parallel striplines of the second group and the striplines of the third group, and the striplines of the striplines of the first group are the first group. Oriented substantially perpendicular to the striplines of the two groups of striplines, wherein the striplines of the third group of striplines are substantially relative to the striplines of the striplines of the first and second groups. Oriented at 45 °, Striplines of the first group are electrically interconnected together at one or more of each of the first and second diagonally opposite edges of each of two or more of four or more patches, Striplines of the second group are electrically interconnected together at one or more of each of the third and fourth diagonally opposite edges of each of two or more of four or more patches, For one or more groups of four patches, the antenna further comprises one tuning stub extending outwardly toward a common point from one corner of each of the four patches constituting one or more groups of patches, wherein One stripline from the third group of striplines interconnects each of the two closest tuning stubs and each tuning stub. The method of claim 1, wherein the patches comprise four or more patches, each patch comprising first and second diagonally opposite edges and third and fourth diagonally opposite edges, The striplines are distributed in a ratio between the parallel striplines of the first group and the parallel striplines of the second group and the striplines of the third group, and the striplines of the striplines of the first group are Oriented substantially perpendicular to the striplines of the stripline of the second group, wherein the striplines of the stripline of the third group are substantially relative to the striplines of the stripline of the first and second group Oriented at 45 °, Striplines of the first group are electrically interconnected together at one or more of the first and second diagonally opposing edges of each of two or more of four or more patches, The second group of striplines are electrically interconnected together at one or more of each of the third and fourth diagonally opposite edges of each of two or more of four or more patches, For four patches of one or more first groups, the antenna further comprises one shorting stub that extends outwardly toward a common point from one corner of each of the four patches constituting one or more groups of patches. Wherein one stripline from the third group of striplines interconnects each of the two closest short stubs and each short stub, For four patches of one or more second groups, the antenna further comprises one tuning stub extending outwardly toward a common point from one corner of each of the four patches constituting one or more groups of patches. Wherein one stripline from the third group of striplines interconnects each of the two closest tuning stubs and each tuning stub, wherein each tuning stub is the interconnection of the respective tuning stubs and the striplines. An antenna 1300 extending beyond the connection point. The antenna of claim 1, wherein the antenna is a linear array antenna forming a first side and a second side, The antenna comprises three or more patches, each patch forming a first corner near a first side and a second corner near a second side, Between two adjacent patches, the striplines electrically interconnect the first edge of each patch and the second edge of the adjacent patch, the two striplines crosswise,  The antenna further includes one or more tuning stubs extending outward from one or more edges of one patch, the edges also connected to a stripline. 2. The device of claim 1, further comprising: at least one patch through at least one transmission line and at least one stripline and at the ground plane to extract electromagnetic energy from the antenna and / or to supply electromagnetic energy to the antenna. Antenna (1900-3300) further comprising one or more supply means connected to. 2. The second conductive element of claim 1, wherein the second conductivity is electrically connected to one or more patches through one or more transmission lines and one or more striplines to extract electromagnetic energy from the antenna and / or to supply electromagnetic energy to the antenna. And at least one supply means having a member and a first conductive member electrically connected to the ground plane. 2. The apparatus of claim 1, electrically coupled to one or more patches via one or more transmission lines and one or more striplines to extract electromagnetic energy from the antenna and / or to supply electromagnetic energy to the antenna, And at least one of a microstrip line electrically connected to the ground plane, and a line coupled to the opening, an SMA probe, and a probe. The apparatus of claim 1, further comprising two or more supply means, each supplying means comprising one of a microstripline, a line coupled to the opening, an SMA probe, a probe, each supply means from the antenna Electrically connected to one or more patches via at least one transmission line and at least one stripline and electrically connected at right angles to the ground plane for extracting electromagnetic energy and / or supplying electromagnetic energy to the antenna. Antennas 2300, 2900, 3200. The method of claim 1, further comprising: at one or more edges of one or more patches through a transmission line connected to a plurality of striplines for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna. An antenna (1900, 2100, 2500) further comprising at least one supply means electrically connected to a ground plane. The method of claim 1, further comprising: at one or more edges of one or more patches through a transmission line connected to a plurality of striplines for extracting electromagnetic energy from the antenna and / or supplying electromagnetic energy to the antenna; Further comprising at least one supply means electrically connected to the ground plane, The transmission line is centered on the second side of the dielectric layer (1900, 2500). The grounding system of claim 1, wherein at least one edge of at least one patch and at ground through a transmission line connected to a plurality of striplines for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna. Further comprising one or more supply means electrically connected to the face, The transmission line is disposed on the second side of the dielectric layer outside of the array of patches. 2. The system of claim 1, wherein the at least one through a first transmission line connected to a plurality of substantially parallel first striplines for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna. First supply means electrically connected to at least one edge of the patch and to the ground plane; And To extract electromagnetic energy from the antenna and / or to supply electromagnetic energy to the antenna, at least one edge of one or more patches through a second transmission line connected to a plurality of substantially parallel second striplines. And second supply means electrically connected to the ground plane; The first transmission line is disposed outside the array of patches and is substantially perpendicular to the first striplines, And a second transmission line disposed outside the array of patches, substantially perpendicular to the second striplines, wherein the first striplines are substantially perpendicular to the second striplines. The plurality of substantially parallel first strips connected to one or more first edges of each of the one or more patches for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna. One or more supply means electrically connected via transmission lines connected to the lines and electrically connected to the ground plane; And Further comprising a plurality of substantially parallel second striplines connected to one or more second edges of each of the one or more patches, The transmission line is generally disposed centrally on the second side of the dielectric layer in the array of patches, The first striplines are substantially perpendicular to the second striplines, and the first edges are diagonally opposite to the second edges. 2. The at least one patch of claim 1, wherein the first transmission line is connected to a plurality of substantially parallel first striplines for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna. First supply means electrically connected to one or more edges of the ground plane and the ground plane; And At one or more edges of one or more patches through a second transmission line connected to a plurality of substantially parallel second striplines for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna and Further comprising a second supply means electrically connected to a ground plane, The first transmission line is substantially perpendicular to the first striplines and is generally disposed on the center of the second side of the dielectric layer in the array of patches,  The second transmission line is substantially perpendicular to the second striplines and is generally disposed on the center of the second side of the dielectric layer in the array of patches, The first striplines are substantially perpendicular to the second striplines, The second transmission line further comprises a bridge generally configured at the intersection of the first and second transmission lines, The bridge draws apertures formed in the dielectric, ground plane, and second dielectric from the second transmission line on each side of the first transmission line to transfer electromagnetic energy across the second transmission line. An antenna (2900) comprising vias extending through the microstrip disposed on the second dielectric. The first and second lines of a first transmission line connected to a plurality of substantially parallel first striplines for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna. First supply means electrically connected to one or more edges of the one or more patches and to the ground plane through two portions; One or more via first and second portions of a second transmission line connected to a plurality of substantially parallel second striplines for extracting electromagnetic energy from the antenna and / or for supplying electromagnetic energy to the antenna. Second supply means electrically connected to one or more edges of the patch and to the ground plane; And Provide electrical continuity between the first and second portions of the first transmission line, such that the transfer of electromagnetic energy between the first and second transmission lines is substantially prohibited, and the first and second portions of the second transmission line Further comprising a directional coupler configured to provide electrical continuity between them; The coupler comprises: a first microstrip longitudinal section defining a first end connected to the first portion of the first transmission line and a second end connected to the first portion of the second transmission line; A second microstrip longitudinal section forming a first end connected to the second portion of the first transmission line and a second end connected to the second portion of the second transmission line; A first microstrip end connecting section connected between the first end of the first longitudinal section and the first end of the second longitudinal section; A second microstrip end connecting section connected between the second end of the first longitudinal section and the second end of the second longitudinal section; And An intermediate microstrip connection section connected between the mid-section of the first longitudinal section and the middle-section of the second longitudinal section, wherein the first, second, and intermediate connection sections are of the first and second type. Such that the centerlines of the directional sections are spaced about 1/4 wavelength apart, the centerlines of the first and intermediate connecting sections are spaced about 1/4 wavelength apart and the centerlines of the second and intermediate connecting sections are spaced about 1/4 wavelength apart. Having a size, the widths of the first and second longitudinal sections and the intermediate sections are determined assuming an impedance of X, and the widths of the first and second end connecting sections are determined assuming an impedance of about 2X, where X is about 25 to 100 ohms, The first transmission line is substantially perpendicular to the first striplines and generally disposed on the center of the second side of the dielectric layer in the array of patches, The second transmission line is substantially perpendicular to the second striplines and is generally disposed on the center of the second side of the dielectric layer in the array of patches, wherein the first striplines are substantially perpendicular to the second striplines. Antenna 3200. Provide electrical continuity between the first and second portions of the first transmission line, such that the transfer of electromagnetic energy between the first and second transmission lines is substantially prohibited, and the first and second portions of the second transmission line A planar microstrip directional coupler configured to provide electrical continuity between them, A first microstrip longitudinal section forming a first end connected to the first portion of the first transmission line and a second end connected to the first portion of the second transmission line; A second microstrip longitudinal section forming a first end connected to the second portion of the first transmission line and a second end connected to the second portion of the second transmission line; A first microstrip end connecting section connected between the first end of the first longitudinal section and the first end of the second longitudinal section; A second microstrip end connecting section connected between the second end of the first longitudinal section and the second end of the second longitudinal section; An intermediate microstrip connection section connected between the midpoint of the first longitudinal section and the midpoint of the second longitudinal section, wherein the first, second, and intermediate connection sections comprise first and second longitudinal sections. The centerlines are spaced about 1/4 wavelength apart, the centerlines of the first and intermediate connecting sections are spaced about 1/4 wavelength apart, and the centerlines of the second and intermediate connecting sections are spaced about 1/4 wavelength apart. Wherein the widths of the first and second longitudinal sections and the middle sections are determined assuming an impedance of X, and the widths of the first and second end connecting sections are determined assuming an impedance of about 2X, where X is A planar microstrip directional coupler that is about 25 to 100 ohms. 28. The planar microstrip directional coupler of claim 27, wherein each of the first and second ends of the first and second longitudinal sections is chamfered at an angle of about 45 degrees. A single dielectric material layer; A ground plane continuous to the first side of the dielectric material; A plurality of patches continuous to the second side of the dielectric material opposite the first side; Supply terminals; And A plurality of stripline conductors for physically connecting the supply terminals to each of the plurality of patches, wherein the cavity formed between the patches, striplines and ground plane has standing waves formed in the cavity, Microstrip array antenna configured to have nodes present in each of said stripline conductors. Attaching a ground plane to the first side of the planar dielectric; And To ensure that standing waves with multiple nodes are formed in the cavity between the patches, the associated conductive material and the ground plane, on the second side of the planar dielectric, opposite the first side, a feed terminal is provided for each radiating patch. Configuring relevant conductive material, supply terminals and radiation patches connecting to the wires; And at least some nodes of the standing wave coincide with a portion of the associated conductive material. 33. The method of claim 30, wherein the associated conductive material is configured as striplines. Attaching a ground plane to the first side of the planar dielectric; And Opposite the first side, to ensure that standing waves with multiple nodes are formed in the cavity between the patches, the associated conductive material and the ground plane to provide a predetermined distribution of electromagnetic power across the radiating patches. On the second side of the planar dielectric, constructing a related conductive material, supply terminal and radiation patches connecting the supply terminal to the respective radiation patches. 33. The method of claim 32, wherein the associated conductive material is configured as striplines and the predetermined distribution is substantially uniform. 33. The method of claim 32, wherein the associated conductive material is configured as striplines, and the predetermined distribution is tapered to minimize the side lobe energy distribution. A single dielectric material layer; A ground plane continuous to the first side of the dielectric material; A plurality of patches continuous to the second side of the dielectric material opposite the first side; Supply terminals; And A plurality of stripline conductors directly interconnecting said supply terminals to each of said plurality of patches, All patches used in the operating mode are planar microstrip array antennas of the same physical size. Through the first and second sets of conductors intersecting in the same plane, the first and second energy sources are physically connected to respective energy sinks, but have different angular orientations. In a method of distributing EM (electromagnetic) energy between the respective energy sinks and the respective energy sinks, Providing a continuous resonant cavity in the plane of the crossing conductors; And Generating first and second standing waves of first and second angular orientations from the first and second EM energy sources, And wherein said nodes of said first and second standing waves occur at the intersection of at least a portion of said first and second sets of intersecting conductors such that the excitation of the two modes is independent of each other. 37. The method of claim 36, wherein the interconnecting conductors are striplines. Ground plane; A surface region comprising a radiation array member, a signal source terminal, and an associated conductive material interconnecting said signal source terminal and said radiation patches; And A resonance signal cavity between the surface area and the ground plane configured to generate standing waves when applying EM (electromagnetic) energy to the antenna, And the nodes of the standing wave are present in both the associated conductive material and the radiation array member. 39. The antenna of claim 38 wherein the radiation array members are patches of conductive material and the associated conductive material comprises stripline members. A plurality of radiating arrangement members in a planar arrangement; Supply terminals in the planar array; A plurality of associated conductive material members in the planar arrangement; And A standing cavity formed in the cavity comprises a resonant cavity continuous in the planar arrangement, configured to have nodes at intersections of two vertical and horizontal striplines, And the supply terminal is physically connected to each of the plurality of substantially equally sized patches by the plurality of related conductive material members. 41. The apparatus of claim 40, wherein the radiation array members are radiation patches and have substantially the same size for maximum directivity; The associated conductive material members are striplines. A microstrip single plane array antenna that can be used without modification for circularly and linearly polarized beam signals, Multiple radial patches in a planar arrangement; First and second supply terminals in the planar arrangement; First and second sets of stripline conductors in the planar arrangement; And A standing cavity formed in the cavity comprises a resonant cavity continuous in the planar arrangement, configured to have nodes coincident with most of the radiation patches and stripline cross-shaped intersections, Each of the supply terminals is physically connected to each of the plurality of substantially equally sized patches by the first and second set of stripline conductors, and the first and second set of stripline conductors And a microstrip single planar array antenna oriented in different angular directions to form crosswise intersections of the plurality of antennas. 43. The microstrip single plane array antenna of claim 42 wherein the radiating patches have substantially the same size for maximum directivity. 44. The antenna of claim 41 or 43 wherein the patches are square. A method of increasing the transmission efficiency of a microstrip array antenna, arranged side by side in a resonant cavity and comprising signal source terminals and radiating patches in a predetermined plane, Electrically connecting the signal source terminal to the respective radiating patches with a plurality of conductive strips; And configuring antenna members such that standing waves occurring in the resonant cavity have nodes at most intersections of the conductive strips in a mode-excited manner such that crosstalk levels are minimized. A dielectric layer forming a first side and a second side; A conductive ground plane disposed on the first side of the dielectric layer; An array of spaced radiating patches disposed on the second side of the dielectric layer; And An antenna (100-3300) comprising at least one interconnect member electrically interconnected at one or more edges of each patch of the arrays and disposed on the second side of the dielectric layer. 47. The antenna of claim 46 wherein the one or more interconnecting members and the patches form one surface of a leakage cavity that operably includes standing waves. 47. The antenna of claim 46 wherein the one or more interconnecting members operate to direct power flow of standing waves formed in the cavity, the boundaries of the cavity being contoured by the dielectric layer. 47. The antenna of claim 46 wherein said at least one interconnect member operates in conjunction with said patches to determine antenna bandwidth. 47. The antenna of claim 46 wherein said at least one interconnect member operates in conjunction with said patches to form a standing wave resonant frequency of a cavity formed within boundaries of said dielectric layer.

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