JP2007533281A - Microstrip array antenna - Google Patents

Abstract

  The microstrip antenna has one dielectric layer with a conductive ground plane disposed on one side and an array of spaced radiating patches disposed on the other side of the dielectric layer. The radiating patch is interconnected with the feed terminal via a stripline element. In response to electromagnetic energy, a higher order standing wave is induced in the antenna, and a directional beam is transmitted from and / or received by the antenna. The dual mode embodiment is such that standing wave nodes occur at the intersection of orthogonally arranged striplines to minimize the cross polarization level of the signal and the crosstalk between the two modes of operation. Configured.

Description

  A single dielectric layer multipatch microstrip array antenna design included in a leaky cavity to distribute EM (electromagnetic) force between a radiating patch and a power supply.

  The present invention relates generally to antennas, and more particularly to microstrip array antennas.

  The number of direct satellite broadcast services around the world has increased significantly, and thus the global demand for antennas with the capacity to receive such broadcast services has also increased. This increased demand has typically been met with reflectors, or “dish” antennas, well known in the art. Reflector antennas are commonly used in residential environments to receive broadcast services such as the transmission of television channel signals from geostationary or equatorial satellites. However, reflector antennas have several drawbacks. For example, it is bulky and relatively expensive to use in a house. In addition, reflector antennas cannot avoid feed leakage and aperture blockage due to the feed assembly, which greatly reduces the aperture efficiency of the reflector antenna, which typically results in only about 55% aperture efficiency.

  Alternative antennas such as microstrip antennas overcome many of the disadvantages associated with reflector antennas. For example, a microstrip antenna requires less space than a reflector antenna, is simple to manufacture, is less expensive, and is more compatible with printed circuit technology. A microstrip array antenna, ie, a microstrip antenna having an array of microstrips, can be used for applications that require high directivity. However, microstrip array antennas typically require a complex microstrip feed network, which contributes a significant feed loss to the overall antenna loss. Furthermore, many microstrip array antennas are limited to single polarization and to transmission or reception of only linearly polarized beams. Such drawbacks are particularly acute in many parts of the world where broadcast services are provided using only circularly polarized beams. In such cases, service recipients must rely on less efficient, more expensive and bulky reflector antennas, or microstrip array antennas using polarizers. However, the polarizer introduces additional power loss into the antenna and produces a relatively low quality radiation pattern. Furthermore, if dual polarization is required, two antennas with single polarization are required.

  Next, what is needed is a low cost, simply manufactured, compact, high aperture efficiency, no complex feed network, single or dual polarized linear or An antenna that can be easily adapted to transmit and receive circularly polarized beams.

  Thus, the present invention is low cost, compact, has high aperture efficiency, does not require a complex feed network, and is easily adapted to transmit and receive dual polarized linearly or circularly polarized beams. Provide an antenna that can. To that end, the microstrip antenna of the present invention is disposed and spaced apart on the other side of the dielectric layer to form a dielectric single layer with a conductive ground plane disposed on one side and a leakage cavity. Includes an array of radiating patches. In response to electromagnetic energy, a directional beam is transmitted and received by an antenna.

  For a more complete understanding of the present invention and the advantages thereof, reference is now made to the following description taken in conjunction with the accompanying drawings.

  In the following description of the drawings, the specific elements illustrated are not necessarily drawn to scale for clarity, and similar or similar elements are designated by the same reference numerals throughout the several views.

  Hereinafter, two types of antennas will be described. One is a linearly polarized antenna having one power supply unit for single mode operation. In this embodiment, no cruciform or crossing stripline conductors are required and the structure is relatively simple. The other is a dual mode antenna with two input feeds that can operate independently of each other and has a cross-shaped or crossing stripline conductor that connects the patch to the feed connector.

  In the dual mode configuration, the antennas act as two antennas superimposed. Such an antenna can use two feed terminals, the stripline conductor of one terminal being orthogonal to the stripline conductor of the other terminal. Each patch of the antenna is connected to a stripline conductor in a first direction at one corner of the patch or at another point capable of exciting two orthogonal modes, and in a second direction at an adjacent corner or point. Connected to (orthogonal) stripline conductors. In this embodiment, the patch and stripline conductors are arranged such that the standing wave node coincides with the stripline intersection to reduce the interferometric polarization level and crosstalk. When a standing wave node is generated in each stripline conductor, a predetermined or predetermined desired electric field distribution is generated.

  For maximum antenna directivity, it is designed to distribute power evenly between the radiating patches. When configured for uniform electric field distribution, all patches have the same physical size and all interconnect striplines can maintain the same dimensions, thus greatly simplifying the design process and manufacturing tolerances Turn into. This is in contrast to prior art designs that require several different parameters on the stripline interconnecting radiating patch elements to obtain a relatively uniform electric field distribution between radiating patches for maximum directivity. Is.

  On the other hand, depending on the application, a tapered distribution across the radiating patch is preferred to reduce side lobes even if the directivity has to be reduced from an optimum value.

  A dual-mode antenna as presented herein generates two orthogonal circularly polarized radiations, or two orthogonal circularly polarized (ie, right and left hand) radiations with some modifications to the feed area. can do. It will be appreciated that a dual mode antenna can simply be used for single mode operation by not using the other port. It should also be appreciated that for optimal results, for a dual mode antenna, the radiating patch must have two-fold symmetry.

  A stripline conductor, or simply a stripline in the art, forms part of the surface of the leaky cavity, and thus facilitates the power flow between the radiating patch elements while at the resonant frequency of the cavity. affect. The stripline acts to properly guide the flow of power so that the leaked power is diverted to the desired direction, ie radiation, while minimizing other elements to maximize antenna efficiency. To do. In prior art antennas, the stripline acts as a conductive path that transmits the traveling wave from the feed to the radiating patch. In the context of this specification, the stripline acts as a channel, bridging the patch and the feed, so that energy flows back and forth, thus creating some form of standing wave on the channel bridge. In the remainder of this document, the term stripline will be used to refer to a power that surrounds the cavity and is on the dielectric surface opposite the ground plane and is in the form of a traveling wave, standing wave or a combination of the two. Applies to any conductive material other than a radiating patch used to guide the flow of water.

  In view of the multiple possible implementations of such a single-dielectric layer antenna using both standing and traveling waves, multiple configurations, from simple to complex configurations, are possible. The configuration is illustrated and described in the following paragraphs.

Unless otherwise specified, λ _o is the wavelength of the EM energy beam in free space (ie, λ _o = c / f, where c is the speed of light in free space and f is the frequency of the beam. Λ _ε is the wavelength of the EM energy beam in the dielectric medium (ie, λ _ε = v / f, where v is the speed of light in the dielectric medium). Is done. In addition, elements referred to herein as “strips”, “patches”, “strip lines”, “stubs” and “transmission lines” are understood to constitute dielectric microstrip, which is approximately 1 mil (0. (001 inch = 0.0254 mm). The ground plane and edge conductors also preferably have a thickness of about 1 mil, but may be thicker if desired (eg, 0 to provide structural support to the individual antennas). 125 inches = 3.175 mm). It should be understood that the thickness is typically measured in a direction perpendicular to the dielectric surface to which the microstrip, ground plane, or edge conductors are individually coupled.

Furthermore, it should be noted that unless otherwise specified, the dielectric material used in accordance with the present invention (other than the cable) is preferably made from a mechanically stable material having a relatively low dielectric constant. The dielectric layer can be suitably multilayered to provide the desired dielectric constant. One dielectric layer, whether composite or not, preferably has a thickness between 0.003λ _ε and 0.050λ _ε , but this may be done to increase bandwidth. It may be thicker.

  Furthermore, it should be noted that in this specification, when referring to a higher order standing wave, this includes one of the higher order standing waves that define modes other than the fundamental mode.

  Further, as used herein (unless otherwise indicated), ground planes, edge conductors, microstrips (eg, strips and patches), etc. may comprise conductive materials such as copper, aluminum, silver and / or gold. Note that it is preferred. Any reference herein to bonding such a conductive material to a dielectric material may include conventional printed circuits, plating, transfer, monolithic microwave integrated circuit (MMIC) technology, chemical etching technology, or any other. Preferably, this can be achieved using any suitable technique. For example, according to chemical etching techniques, the dielectric layer can be coated on one of the conductive materials described above. The conductive material is then selectively etched away from the dielectric layer using conventional chemical etching techniques, thereby defining any microstrip pattern described herein. Optionally, the second dielectric layer on the surface of the dielectric having the conductive material using any suitable technique, such as creating a bond with a very thin (eg, 1.5 mil) thermal bond film. Can be combined.

Furthermore, it should be noted that the following description of the invention refers to the use of calculations and analysis. For example, in a paper entitled “Planar dual-band microstrip antenna” published in IEEE Transactions on Antennas and Propagation (Vol. 43, pp. 892-895, August 1995). S. Lee, V.C. Nalbandian and F.M. Schwering, and “Double-layer Microstrip Antenna” published in 1998 as a doctoral dissertation at the Department of Electrical Engineering, Southern Methodist University. H. Such as the cavity model and moment method described by Hsieh. Both of these articles are hereby incorporated by reference in their entirety and are collectively referred to hereinafter as “Lee and Hsieh”.

(Medium gain antenna applications (for base station antennas))
1 to 3
Referring to FIGS. 1 and 2, reference numeral 100 refers generally to a planar microstrip array antenna that implements features of the present invention that transmit and receive beams. The antenna 100 preferably includes a substantially square dielectric layer 112. The width 102 and length 102 of the layer 112 is determined by the number and spacing of the used patches described below and preferably extends beyond the outer edge of the patch 120 by a width and length 102a of at least 0.50λ _ε. .

As shown most clearly in FIG. 2, the dielectric layer 112 defines a bottom side 112a to which the conductive ground plane 116 is coupled, and an upper side 112b to which the array of conductive radiating patches 120 and the central radiating patch 122 are coupled. Thus, a radiation cavity is formed in the dielectric layer 112 between the patches 120, 122, the strip line 124 and the ground plane 116. Returning to FIG. 1, the patches 120 and 122 are substantially square in shape, each having four corners 120a and four radial edges 120b, each edge having a length 120c of about 0.50λ _ε. preferable. Patches 120 and 122 electrically interconnect with an array of substantially parallel conductive striplines 124 through one corner 120a or two diagonally opposite corners 120a. Four tuning stubs 126 extend perpendicularly from the two striplines 124. Patches 120 and 122 are preferably spaced apart by a center-to-center distance 160 of about 1.0λ _ε . Patches 120 and 122 are preferably arranged as a square array on top surface 112b, which preferably has the same number of columns and rows as patches 120 and 122, which is illustrated in FIG. And a total of 25 patches 120 and 122 are illustrated as a square array comprising the antenna 100. The width 184 of each stripline 124 and the width and length of each stub 126 are preferably determined assuming a characteristic impedance of about 50-200 ohms. The antenna 100 is preferably provided with a shortening pin 178 that electrically connects the ground plane 116 to the central patch 122 to suppress unwanted mode excitation. The antenna 100 may also include additional shortening pins (not shown) that connect the ground plane 116 to the patch 120 to further suppress unwanted mode excitation. Alternatively, in some cases it may be preferable to delete one or all of the shortened pins 28 from the antenna 100.

  To obtain optimum performance at a particular frequency, the dimensions of patches 120 and 122, stripline 124, stub 126, opening 150, and center-to-center distance 160 are high within the antenna cavity formed in dielectric 112. The next standing wave is generated and therefore the electric fields radiating from the radiating edge 120b are individually calculated to intensify and interfere with each other, giving the desired antenna characteristics such as high directivity. The number of patches 120 and 122 determines not only the overall size of the antenna 100 but also its directivity. The level of the side lobe of the antenna 100 is determined by the electric field distribution between the radiating elements 120. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and position of each patch 120 and 122 and the feed scheme. In order to achieve high directivity, the electric field distribution between the radiating elements should be as uniform as possible. The above calculations and analyzes use techniques such as, for example, the cavity model method and the moment method described by Lee and Hsieh and will not be described in further detail here.

  A conventional SMA (microminiature A) probe 170 is provided to transmit and receive the beam. Each SMA probe 170 has an outer conductor 172 electrically connected to the ground plane 116 and an interior electrically connected to the center patch 122 (in order to deliver EM energy to and / or from the antenna 100). Or a power feed) conductor 174. Probe 170 is positioned along the diagonal of patch 122 in the vicinity of stripline 124 to optimize the impedance matching of antenna 100. The probe 170 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the above connections. For example, a conductive adhesive (not shown) can be used to bond between the inner conductor 174 and the center patch 122 to maintain contact therebetween, with the SMA probe 170 passing through the ground plane 116. When doing so, an appropriate seal | sticker (not shown) can be provided and a connection part can be airtightly sealed. It is understood that the other end of the SMA probe 170 that is not connected to the antenna 100 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want to be.

  In operation, the antenna 100 can be used to transmit and receive linearly polarized (LP) EM beams. To illustrate how to use the antenna 100 to receive a beam, the antenna 100 is positioned within the home to receive a beam carrying a television signal in a predetermined frequency band or channel from a stationary or equatorial satellite. Can be oriented. The antenna 100 is thus oriented by directing the top surface 112b toward the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 100 are appropriately sized to receive the beam, the beam passes through aperture 150 and induces a standing wave that resonates within dielectric layer 112. Standing waves induced in the resonant cavity defined by the dielectric layer 112 communicate with a receiver, such as a decoder (not shown), through the SMA probe 170. It is well known that antennas transmit and receive signals to each other. Accordingly, it can be understood that the operation of the antenna 100 for signal transmission is mutually the same as the antenna operation for signal reception. Therefore, signal transmission by the antenna 100 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 1 and 2 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 120 can be provided to narrow the beam, or the number of patches 120 used can be reduced to reduce the physical space required for the antenna 100 of the present invention. The embodiment of FIGS. 1 and 2 can be configured with a triangular structure for use in a telecommunications cell. The stub 126 can be reconfigured to form an alternative embodiment, one of which is illustrated and described in more detail below with respect to FIG.

  FIG. 3 shows details of a single mode antenna 300 according to an alternative embodiment of the present invention. Since antenna 300 includes many elements that are identical to that of antenna 100, those elements are referred to by the same reference numerals and will not be described in further detail. According to the embodiment of FIG. 3, in contrast to the embodiment of FIG. 1, four stubs 126 are replaced by two stubs 326, which are outward along a line extending diagonally of the central patch 122. Extend. The operation of the antenna 300 shown in FIG. 3 is substantially the same as the operation of the antenna 100 shown in FIG.

4 to 7
Referring to FIGS. 4 and 5, reference numeral 400 refers generally to a planar microstrip array antenna that implements features of the present invention for dual mode operation such as transmission and reception of EM beams. The antenna 400 preferably includes a substantially square dielectric layer 412. The width 402 and length 402 of layer 412 is determined by the number of patches used, described below, and preferably extends beyond the outer edge of patch 420 by a width and length 402a of at least 0.50λ _ε .

As most clearly shown in FIG. 5, the dielectric layer 412 defines a bottom side 412a to which a conductive ground plane 416 is coupled and an upper side 412b to which an array of conductive radiating patches 420 and a central radiating patch 422 are coupled. Thus, a resonant cavity is formed in the dielectric layer 412 between the patches 420 and 422, the striplines 424 and 424, and the ground plane 416. Returning to FIG. 4, patches 420 and 422 are substantially square in shape, each having four corners 420a and four radial edges 420b, each edge having a length 420c of approximately 0.50λ _ε . As seen in FIG. 4, patches 420 and 422 include substantially parallel vertical conduction coupled to an array of substantially parallel horizontal conductive striplines 424 and dielectric layer 412 via corners 420a. Electrically interconnects with an array of striplines 426. Four adjustment stubs 428 extend diagonally outward from the corners 420 a of the central patch 422 and from the horizontal and vertical striplines 424 and 426, which are also coupled to the dielectric layer 412. Patches 420 and 422 are preferably spaced apart by a center distance 460 slightly less than 1.0λ _ε. Patches 420 and 422 are arranged as a square array on top surface 412 and may have an odd number of equal number of rows and columns of patches 420 and 422 (as viewed at 45 ° to the horizontal in FIG. 4). This is preferably illustrated in FIG. 4 as a square array having 5 columns and 5 rows of patches 420 and 422, with a total of 25 patches 420 and 422 constituting the antenna 400. The width 484 (FIG. 4) of each stripline 424 and 426 and the width of each stub 428 are preferably determined assuming a characteristic impedance of about 50-200 ohms. The antenna 400 is preferably provided with a shortened pin 478 that electrically connects the ground plane 416 to the central patch 422 to suppress unwanted mode excitation. The antenna 400 may also include additional shortening pins (not shown) that connect the ground plane 416 to the patch 420 to further suppress undesirable mode excitation. Alternatively, in some cases it may be preferable to remove one or all of the shortened pins 478 from the antenna 400.

  To obtain optimum performance at a particular frequency, the dimensions of patches 420 and 422, striplines 424 and 246, stub 428, opening 450, and center-to-center distance 460 are within the antenna cavity formed in dielectric 412. High-order standing waves are generated at the same time, and thus the electric fields radiating from the radiation edge 420b are individually calculated so as to strengthen each other and interfere with each other.

  The number of patches 420 and 422 determines not only the overall size of the antenna 400 but also its directivity. The level of the side lobe of the antenna 400 is determined by the electric field distribution between the radiating elements 420. Thus, antenna characteristics such as directivity and sidelobe levels are controlled by the size and position of each patch 420 and 422 and the feeding scheme. To achieve high directivity, the electric field distribution between the radiating elements 420 should be as uniform as possible. Dielectric layer 412 has field zero points in patches 420 and 422 and connecting striplines 424 and 426. The above calculations and analyzes are based on, for example, the cavity model described by Lee and Hsieh, and Ansoft Corp., Pittsburgh, PA. Will not be described in further detail here, since techniques such as the product moment method described in software Ensemble® available from www.softwareengine.com.

  Preferably, two conventional SMA probes 470 are provided for dual mode operation such as beam transmission and reception. Each SMA probe 470 has an outer conductor 472 electrically connected to the ground plane 416 and an interior electrically connected to the center patch 422 (in order to deliver EM energy to and / or from the antenna 400). Or a power feed) conductor 474. Probe 470 is positioned along the diagonal of patch 422 in the vicinity of striplines 424 and 426 to optimize the impedance matching of antenna 400 and reduce crosstalk and interfering polarization. Probe 470 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 474 and the center patch 422 to maintain contact therebetween, with the SMA probe 470 passing through the ground plane 416. In this case, an appropriate seal (not shown) can be provided to hermetically seal the connecting portion. It is understood that the other end of the SMA probe 470 that is not connected to the antenna 400 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want to be.

  In operation, the antenna 400 can be used to transmit and receive linearly polarized (LP) EM beams. To illustrate how to use the antenna 400 to receive a beam, the antenna 400 is positioned in the home to receive a beam carrying television signals in a predetermined frequency band or channel from a stationary or equatorial satellite. Can be oriented. The antenna 400 is thus oriented by directing the top surface 412b toward the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 400 are appropriately sized to receive the beam, the beam passes through aperture 450 and induces a standing wave that resonates within dielectric layer 412. Standing waves induced in the resonant cavity defined by the dielectric layer 412 communicate with a receiver such as a decoder (not shown) through the SMA probe 470.

  Within the antenna 400, the vertical mode excitation is orthogonal to that of the horizontal mode, so crosstalk between the two input signals is minimized. That is, two orthogonal vertical and horizontal modes can be excited separately.

  It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the signal transmission antenna 400 is mutually the same as the signal reception antenna operation. Therefore, signal transmission by antenna 400 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 4 and 5 are intended to illustrate rather than to limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 420 can be provided to narrow the beam, or the number of patches 420 used can be reduced to reduce the physical space required for the antenna 400 of the present invention. An embodiment that reduces the number of patches used is illustrated in FIGS. In another example, one of the two SMA probes 470 can be removed (or not attached) in single mode operation for transmitting and receiving EM beams. The antenna 400 can also be used to transmit and receive circularly polarized (CP) EM beams. In some cases, it may be preferable to delete the shortening pin 478 from the antenna 400.

8 to 9
Referring to FIGS. 8 and 9, reference numeral 800 refers generally to a planar microstrip array antenna that implements features of the present invention for dual mode operation such as transmission and reception of EM beams. The antenna 800 preferably includes a substantially square dielectric layer 812. The width 802 and length 802 of layer 812 is determined by the number of used patches 820 described below, and preferably extends beyond the outer edge of patch 820 by a width and length 802a of at least 0.50λ _ε .

As shown most clearly in FIG. 9, the dielectric layer 812 includes a bottom side 812a to which a conductive ground plane 816 is coupled, and an upper side 812b to which an array of conductive radiating patches 820 and four central radiating patches 822 are coupled. Define and form a resonant cavity in the dielectric layer 812 between the patches 820 and 822, the striplines 824, 826, and the ground plane 816. Returning to FIG. 8, patches 820 and 822 are substantially square shaped, each having four corners 820a and four radial edges 820b, each edge having a length 820c of about 0.50λ _ε . As seen in FIG. 8, the patches 820 and 822 are substantially parallel vertical arrays coupled to an array of substantially parallel horizontal conductive striplines 824 and a dielectric layer 812 via corners 820a. Electrically interconnects with an array of conductive striplines 826. An adjustment stub 828 extends diagonally outward from the corner 820 a of each center patch 822 toward the center of the antenna 800. Stub 828 is also coupled to dielectric layer 82. Patches 820 and 822 are preferably spaced apart by a center distance 860 slightly less than 1.0λ _ε. Patches 820 and 822 are arranged as a square array on top surface 812b and have an even number of equal number of row and column patches 820 and 822 (as viewed at an angle of 45 ° to the horizontal in FIG. 8). Preferably, this is illustrated in FIG. 8 as a square array having four columns and four rows of patches 820 and 822, with a total of 16 patches 820 and 822 constituting the antenna 800. The width 884 (FIG. 8) of each stripline 824 and 826 and the width and length of each stub 828 are preferably determined assuming a characteristic impedance of about 50-200 ohms. The antenna 800 is preferably provided with a shortening pin 878 that electrically connects the ground plane 816 to each central patch 822 to suppress unwanted mode excitation. The antenna 800 may also include additional shortening pins (not shown) that connect the ground plane 816 to the patch 820 to further suppress unwanted mode excitation. Alternatively, in some cases it may be preferable to remove one or all of the shortened pins 878 from the antenna 800.

  For optimum performance at a particular frequency, the dimensions of patches 820 and 822, striplines 824 and 826, stub 828, opening 850, and center-to-center distance 860 are within the antenna cavity formed in dielectric 812. High-order standing waves are generated at the same time, and thus the electric fields radiating from the emission edge 820b are calculated individually so as to intensify and interfere with each other.

  The number of patches 820 and 822 determines not only the overall size of the antenna 800 but also its directivity. The level of the side lobe of antenna 800 is determined by the electric field distribution between radiating elements 820 and 822. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and position of each patch 820 and 822 and the feed scheme. To achieve high directivity, the electric field distribution between the radiating elements 820 and 822 should be as uniform as possible. The above calculations and analyzes are performed, for example, by the cavity model described by Lee and Hsieh, and for example by Anasoft Corp. Since a technique such as the product moment method described in software Ensemble (TM) available from is used, it will not be described in further detail here.

  Two conventional SMA probes 870 are preferably provided for dual mode operation such as beam transmission and reception. Each SMA probe 870 has an outer conductor 872 electrically connected to the ground plane 816 and an interior electrically connected to the center patch 822 (in order to deliver EM energy to and / or from the antenna 800). Or a power feed) conductor 874. Therefore, the two SMA probes 870 are connected to the two adjacent center patches 822 selected. Probe 870 is positioned along the diagonal of two selected individual center patches 822 in the vicinity of striplines 824 and 826 to optimize the impedance matching of antenna 800 and reduce crosstalk and interfering polarization. Probe 870 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 874 and the center patch 822 to maintain contact therebetween, and the SMA probe 870 passes through the ground plane 816. When doing so, an appropriate seal | sticker (not shown) can be provided and a connection part can be airtightly sealed. It is understood that the other end of the SMA probe 870 that is not connected to the antenna 800 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want.

  In operation, the antenna 800 can be used to transmit and receive linearly polarized (LP) EM beams. To illustrate how to use the antenna 800 to receive a beam, the antenna 800 is positioned within the home to receive a beam carrying a television signal in a predetermined frequency band or channel from a stationary or equatorial satellite. Can be oriented. The antenna 800 is thus oriented by directing the top surface 812b toward the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 800 are sized appropriately to receive the beam, the beam passes through aperture 850 and induces a standing wave that resonates within dielectric layer 812. Standing waves induced in a resonant cavity defined in the dielectric layer 812 are communicated through a SMA probe 870 to a receiver such as a decoder (not shown).

  Within antenna 800, the vertical mode excitation is orthogonal to that of the horizontal mode, so crosstalk between the two input signals is minimized. That is, two orthogonal vertical and horizontal modes can be excited separately.

  It is well known that antennas transmit and receive signals to each other. Accordingly, it can be understood that the operation of the antenna 800 for signal transmission is mutually the same as the antenna operation for signal reception. Therefore, signal transmission by antenna 800 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 8 and 9 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 820 can be provided to narrow the beam, or the number of patches 820 used can be reduced to reduce the physical space required for the antenna 800 of the present invention. In another example, one of the two SMA probes 870 can be removed (or not attached) in single mode operation of transmitting and receiving EM beams. The antenna 800 can also be used to transmit and receive circularly polarized (CP) EM beams.

10 to 12
Referring to FIGS. 10-12, reference numeral 1000 refers generally to a planar microstrip array antenna that implements features of the present invention for dual mode operation such as transmission and reception of EM beams. Antenna 1000 preferably includes first and second dielectric layers 1012 and 1014 that are substantially square. The width 1002 and length 1002 of layers 1012 and 1014 are determined by the number of used patches 1020 and 1022 described below and extend beyond the outer edge of patch 1020 by a width and length 1002a of at least 0.50λ _ε. It is preferable.

  As shown most clearly in FIG. 11, the dielectric layer 1012 includes a bottom side 1012a to which a conductive ground plane 1016 is coupled, and an upper side 1012b to which an array of conductive radiating patches 1020 and four central radiating patches 1022 are coupled. Define and form a resonant cavity between the patches 1020 and 1022, the striplines 1024 and 1026, and the ground plane 1016 in the dielectric layer 1012. The second dielectric 1014 is coupled to the upper side 1012b of the dielectric 1012 so that the patches 1020 and 1022 are inserted between the dielectrics 1012 and 1014.

As shown most clearly in FIG. 12, the patches 1020 and 1022 are substantially square shaped, each having four corners 1020a and four radial edges 1020b, each having a length 1020c of about 0.50λ _ε. Have. As seen in FIG. 12, patches 1020 and 1022 are substantially inserted through corners 1020a into an array of substantially parallel horizontal conductive striplines 1024 and between dielectric layers 1012 and 1014. Electrically interconnects with an array of parallel vertical conductive striplines 1026. Stubs 1025 inserted between dielectric layers 1012 and 1014 extend from the corners 1020a of each patch 1020 and 1022 onto individual striplines 1024 and 1026. A stripline 1027 inserted between the dielectric layers 1012 and 1014 electrically connects each stub 1025 to the two nearest stubs 1025. A tuning stub 1028 inserted between dielectric layers 1012 and 1014 extends outwardly from one stub 1025 of each central patch 1022 toward the center of antenna 1000 for impedance matching.

Patches 1020 and 1022 are preferably spaced apart by a center distance 1060 slightly less than 1.0λ _ε. Patches 1020 and 1022 are arranged as a square array on top surface 1012b and have an even number of equal number of rows and columns of patches 1020 and 1022 (viewed at 45 ° to the horizontal in FIG. 10). Preferably, this is illustrated in FIG. 12 as a square array having 4 columns and 4 rows of patches 1020 and 1022, with a total of 16 patches 1020 and 1022 comprising antenna 1000. The width 1084 (FIG. 10) of each stripline 1024, 1026 and 1027 and the width and length of each stub 1025 and 1028 are preferably determined assuming a characteristic impedance of about 50-200 ohms. Antenna 1000 is optionally provided with a shortened pin (not shown) that electrically connects ground plane 1016 to one or more patches 1020 and / or 1022 to suppress excitation of undesirable modes. be able to. Note that the use of a stub such as 1025 in a planar antenna as shown provides impedance matching.

  The dimensions of patches 1020 and 1022, striplines 1024, 1026 and 1027, stubs 1025 and 1028, openings 1050, and center-to-center distance 1060 are formed in dielectric 1012 to obtain optimum performance at a particular frequency. The higher order standing waves are generated in the antenna cavity, and thus the electric fields radiating from the radiating edge 1020b are calculated individually so as to intensify and interfere with each other. The number of patches 1020 and 1022 determines not only the overall size of the antenna 1000, but also its directivity. The sidelobe level of antenna 1000 is determined by the electric field distribution between radiating elements 1020 and 1022. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and location of each patch 1020 and 1022 and the feed scheme. To achieve high directivity, the electric field distribution between the radiating elements 1020 and 1022 should be as uniform as possible. Within dielectric layers 1012 and 1014 there are field zero points within patches 1020 and 1022 and connecting striplines 1024 and 1026. The above calculations and analyzes are performed, for example, on the cavity model described by Lee and Hsieh, and for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product moment method described in software Ensemble® available from www.softwareengine.com.

  Two conventional SMA probes 1070 are preferably provided for dual mode operation such as beam transmission and reception. As shown most clearly in FIG. 11, each SMA probe 1070 includes an outer conductor 1072 electrically connected to a ground plane 1016, and ground, for delivering EM energy to and / or from the antenna 1000. It includes an internal (or feed) conductor 1074 that extends through an opening formed in the plane 1016 and the two central patches 1022 and is electrically connected to the patch 1023. Patch 1023 is preferably square, and its sides have a length of about 2 millimeters (mm) to about 5 mm, typically about 2.5 mm to about 4.5 mm, preferably about 3 mm. Therefore, the two SMA probes 1070 are connected to the two adjacent center patches 1022 selected. Probe 1070 is positioned along the diagonal of two selected individual center patches 1022 in the vicinity of striplines 1024 and 1026 to optimize the impedance matching of antenna 1000 and reduce crosstalk and interfering polarization. Probe 1070 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to bond between the inner conductor 1074 and the selected center patch 1022 to maintain contact therebetween, and the SMA probe 1070 is connected to the ground plane. When passing through 1016, an appropriate seal (not shown) can be provided to hermetically seal the connection. It is understood that the other end of the SMA probe 1070 that is not connected to the antenna 1000 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want.

  In operation, the antenna 1000 can be used to transmit and receive linearly polarized (LP) EM beams. To illustrate how to use the antenna 1000 to receive a beam, the antenna 1000 is positioned within the home to receive a beam carrying television signals in a predetermined frequency band or channel from a stationary or equatorial satellite. Can be oriented. The antenna 1000 is thus oriented by directing the top surface 1012b towards the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 1000 are appropriately sized to receive the beam, the beam passes through aperture 1050 (FIG. 11) and induces a standing wave, which is in dielectric layer 1012. Resonates at. Standing waves induced in a resonant cavity defined in dielectric layer 1012 are communicated through a SMA probe 1070 to a receiver such as a decoder (not shown).

  Within the antenna 1000, the vertical mode excitation is orthogonal to that of the horizontal mode, so crosstalk between the two input signals is minimized. That is, two orthogonal vertical and horizontal modes can be excited separately.

  It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the antenna 1000 for signal transmission is mutually the same as the antenna operation for signal reception. Therefore, signal transmission by antenna 1000 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 10-12 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 1020 can be provided to narrow the beam, or the number of patches 1020 used can be reduced to reduce the physical space required for the antenna 1000 of the present invention. In another example, one of the two SMA probes 1070 can be removed (or not attached) in single mode operation for transmission and reception of EM beams. The antenna 1000 can also be used to transmit and receive circularly polarized (CP) EM beams.

13 to 15
Referring to FIGS. 13-15, reference numeral 1300 refers generally to a planar microstrip array antenna that implements features of the present invention for dual mode operation such as transmission and reception of EM beams. The antenna 1300 preferably includes first and second dielectric layers 1312 and 1314 that are substantially square. The width 1302 and length 1303 of layers 1312 and 1314 is determined by the number of used patches 1320 and 1322 described below and extends beyond the outer edge of patch 1320 by a width and length 1302a of at least 0.50λ _ε. It is preferable.

  As shown most clearly in FIG. 14, the dielectric layer 1312 includes a bottom side 1312a to which a conductive ground plane 1316 is coupled, and preferably twelve external conductive radiating patches 1320 (FIG. 13), eight intermediate radiating patches. 1321, and an upper side 1312b to which an array of four internal radiating patches 1322 is coupled to form a resonant cavity between the patches 1320, 1321 and 1322, the striplines 1324 and 1352, and the ground plane 1316 within the dielectric layer 1312. Form. The second dielectric 1314 is coupled to the upper side 1312b of the dielectric 1312 so that the patches 1320, 1321 and 1322 are inserted between the dielectrics 1312 and 1314.

As most clearly shown in FIG. 15, patches 1320, 1321 and 1322 are substantially square in shape, each having four corners 1320a and four radial edges 1320b, each having a length of approximately 0.50λ _ε . 1320c. As seen in FIG. 15, patches 1320, 1321 and 1322 are inserted between dielectric layers 1312 and 1314 via corners 1320a (as seen in FIGS. 13 and 15) vertical and horizontal conductive strips. Electrically interconnected through an array of lines 1324. An inter-patch area 1352 is defined in each space that is delimited by the stripline 1324 and does not include the patch 1320, 1321, or 1322. Stubs 1325 inserted between dielectric layers 1312 and 1314 pass through individual striplines 1324 into inter-patch areas 1352 and adjacent to inter-patch areas 1352 bounded by at least one internal patch 1322. Each patch 1320, 1321 and 1322 extends from each corner 1320a. A stripline 1326 inserted between the dielectric layers 1312 and 1314 electrically connects each stub 1325 to the two nearest stubs 1325. An adjustment stub 1328 inserted between the dielectric layers 1312 and 1314 is provided for each patch 1321 adjacent to the inter-patch area 1352 delimited by two intermediate patches 1321 and two internal patches 1322 for impedance matching. And 1322 from each stub 1325.

Patches 1320, 1321 and 1322 are preferably only center-to-center distance 1360 of about 1.0Ramuda _epsilon spaced. Patches 1320, 1321 and 1322 are preferably arranged as a square array on top surface 1312b and have an even number of rows and columns of patches 1320, 1321 and 1322. The width 1384 (FIG. 13) of each stripline 1324 and 1326 and the width and length of each stub 1325 and 1328 are preferably determined assuming a characteristic impedance of about 50-200 ohms. Antenna 1300 optionally includes a shortened pin (not shown) that electrically connects ground plane 1316 to one or more patches 1320, 1321, and / or 1322 to suppress excitation of undesirable modes. Can be arranged.

  For optimum performance at a particular frequency, the dimensions of patches 1320, 1321 and 1322, striplines 1324 and 1326, stubs 1325 and 1328, openings 1350 and area 1352, and center-to-center distance 1360 are within dielectric 1312. Are individually calculated so that higher-order standing waves are generated in the antenna cavities formed in the, and thus the electric fields radiating from the radiating edge 1320b mutually intensify and interfere with each other. The number of patches 1320, 1321, and 1322 determines not only the overall size of the antenna 1300 but also its directivity. The level of the side lobe of the antenna 1300 is determined by the electric field distribution between the radiating elements 1320, 1321 and 1322. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the location and feed scheme of each patch 1320, 1321 and 1322. To achieve high directivity, the electric field distribution between the radiating elements 1320, 1321 and 1322 should be as uniform as possible. Within dielectric layer 1312, there are field zero points between patches 1320, 1321 and 1322 and connecting striplines 1324 and 1326 and ground plane 1316. The above calculations and analyzes are performed, for example, on the cavity model described by Lee and Hsieh, and for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product moment method described in software Ensemble® available from www.softwareengine.com.

  Two conventional SMA probes 1370 are preferably provided for dual mode operation such as beam transmission and reception. As shown most clearly in FIG. 14, each SMA probe 1370 includes an outer conductor 1372 electrically connected to a ground plane 1316 and a ground for delivering EM energy to and / or from the antenna 1300. It includes an internal (or feed) conductor 1374 that extends through a plane 1316 and an opening formed in two internal patches 1322 and is electrically connected to patch 1323. The patch 1323 is preferably square, and its sides have a length of about 2 mm to about 5 mm, typically about 2.5 mm to about 4.5 mm, preferably about 3 mm. Therefore, two SMA probes 1370 are connected to two adjacent center patches 1322. Probe 1370 is positioned along the diagonal of two selected individual center patches 1322 in the vicinity of stripline 1324 to optimize antenna 1300 impedance matching and reduce crosstalk and interfering polarization. The probe 1370 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 1374 and the selected center patch 1322 to maintain contact therebetween, and the SMA probe 1370 is connected to the ground plane. When passing 1316, an appropriate seal (not shown) can be provided to hermetically seal the connection. It is understood that the other end of the SMA probe 1370 that is not connected to the antenna 1300 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want.

  In operation, the antenna 1300 can be used to transmit and receive linearly polarized (LP) EM beams. To illustrate how to use antenna 1300 to receive a beam, antenna 1300 is positioned within a home to receive a beam carrying a television signal in a predetermined frequency band or channel from a stationary or equatorial satellite. Can be oriented. The antenna 1300 is thus oriented by directing the top surface 1312b towards the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 1300 are sized appropriately to receive the beam, the beam passes through aperture 1350 and area 1352 to induce a standing wave, which is in dielectric layer 1312. Resonates. Standing waves induced in the resonant cavity defined by dielectric layer 1312 connect through SMA probe 1370 to a receiver such as a decoder (not shown).

  Within the antenna 1300, the vertical mode excitation is orthogonal to that of the horizontal mode, thus minimizing crosstalk between the two input signals. That is, two orthogonal vertical and horizontal modes can be excited separately.

  It is well known that antennas transmit and receive signals to each other. Accordingly, it can be understood that the operation of the antenna 1300 for signal transmission is mutually the same as the antenna operation for signal reception. Therefore, signal transmission by antenna 1300 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 13-15 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 1320 can be provided to narrow the beam, or the number of patches 1320 used can be reduced to reduce the physical space required for the antenna 1300 of the present invention. In another example, one of the two SMA probes 1370 can be removed (or not attached) in single mode operation for transmitting and receiving EM beams. The antenna 1300 can also be used to transmit and receive circularly polarized (CP) EM beams.

16 to 18
Referring to FIGS. 16-18, reference numbers 1600 and 1800 refer generally to a linear microstrip array antenna that implements features of the present invention for dual mode operation such as transmission and reception of EM beams. The linear array antenna 1600 is configured to produce a narrow beam in the direction of the array but a wide beam in the direction perpendicular to the array. The antenna 1600 preferably includes a substantially rectangular dielectric layer 1612. The length 1602 of the layer 1612 is determined by the number of used patches 1620 described below and preferably extends beyond the outer edge of the patch 1620 by a length 1602a and a length 1604a of at least 0.50λ _ε .

  As shown most clearly in FIG. 17, the dielectric layer 1612 includes a bottom side 1612a to which a conductive ground plane 1616 is coupled, and an upper side to which an array of conductive radiating patches 1620 (FIG. 16) and a central radiating patch 1622 are coupled. 1612b is defined to form a resonant cavity in the dielectric layer 1612 between the patches 1620 and 1622, the stripline 1620, and the ground plane 1616. (Note that the ground plane 1616 in FIG. 17 must cover the entire area of the bottom surface of the dielectric slab.)

Returning to FIG. 16, patches 1620 and 1622 are substantially square shaped, each having four corners 1620a and four radial edges 1620b, each having a length 1620c of approximately 0.50λ _ε . As seen in FIG. 16, patches 1620 and 1622 are electrically interconnected via corners 1620 a coupled to dielectric layer 1612 and crossed conductive striplines 1624. Two adjustment stubs 1628 extend diagonally outward from the two corners 1620 a of the central patch 1622 and are also coupled to the dielectric layer 1612. Patches 1620 and 1622 are spaced apart by a slightly smaller center-to-center distance 1660, preferably 1.0λ _ε . Patches 1620 and 1622 are preferably arranged as an array on top surface 1612b, illustrated in FIG. 16 as having two patches 1620 on each side of one patch 1622, for a total of five patches. 1620 and 1622 constitute the antenna 1600. The width 1684 of each stripline 1624 (FIG. 16) and the length and width of each stub 1628 are preferably determined assuming a characteristic impedance of about 50-200 ohms. The antenna 1600 is preferably provided with a shortened pin 1678 (not shown) that electrically connects the ground plane 1616 to the central patch 1622 to suppress unwanted mode excitation. The antenna 1600 may also include additional shortening pins (not shown) that connect the ground plane 1616 to the patch 1620 to further suppress unwanted mode excitation. Alternatively, in some cases, it may be preferable to remove one or all shortened pins 1678 from the antenna 1600.

  To obtain optimum performance at a particular frequency, the dimensions of patches 1620 and 1622, stripline 1624, stub 1628, opening 1650, and center-to-center distance 1660 are high within the antenna cavity formed in dielectric 1612. The next standing wave is generated and is thus calculated individually so that the electric fields radiating from the radiating edge 1620b intensify and interfere with each other. The number of patches 1620 and 1622 determines not only the overall size of the antenna 1600 but also its directivity. The sidelobe level of antenna 1600 is determined by the electric field distribution at radiating elements 1620 and 1622. Thus, antenna characteristics such as directivity and sidelobe levels are controlled by the size and position of each patch 1620 and 1622 and the feed scheme. To achieve high directivity, the electric field distribution in the radiating elements 1620 and 1622 should be as uniform as possible. The above calculations and analyzes are performed, for example, on the cavity model described by Lee and Hsieh, and for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product moment method described in software Ensemble® available from www.softwareengine.com.

  Two conventional SMA probes 1670 are preferably provided for dual mode operation such as beam transmission and reception. Each SMA probe 1670 includes an outer conductor 1672 that is electrically connected to ground plane 1616 and an interior that is electrically connected to center patch 1622 to deliver EM energy to and / or from antenna 1600. Or a power feed) conductor 1674. Probe 1670 is positioned along the diagonal of patch 1622 in the vicinity of stripline 1650 to optimize the impedance matching of antenna 1600 and reduce crosstalk and interfering polarization. Probe 1670 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 1674 and the central patch 1622 to maintain contact therebetween, and the SMA probe 1670 passes through the ground plane 1616. In this case, an appropriate seal (not shown) can be provided to hermetically seal the connecting portion. It is understood that the other end of the SMA probe 1670 that is not connected to the antenna 1600 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want.

  In operation, antenna 1600 can be used to transmit and receive linearly polarized (LP) EM beams. The antenna 1600 is thus oriented by directing the top surface 1612b towards the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 1600 are appropriately sized to receive the beam, the beam passes through aperture 1650 and induces a standing wave that resonates within dielectric layer 1612. Standing waves induced in a resonant cavity defined in dielectric layer 1612 connect through a SMA probe 1670 to a receiver such as a decoder (not shown).

  Within antenna 1600, the vertical mode excitation is orthogonal to that of the horizontal mode, so crosstalk between the two input signals is minimized. That is, two orthogonal vertical and horizontal modes can be excited separately.

  It is well known that antennas transmit and receive signals to each other. Accordingly, it can be understood that the operation of the antenna 1600 for signal transmission is mutually the same as the antenna operation for signal reception. Accordingly, signal transmission by antenna 1600 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 16-18 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 1620 can be provided to narrow the beam, or the number of patches 1620 used can be reduced to reduce the physical space required for the antenna 1600 of the present invention. The antenna 1600 can also be used for transmission and reception of circularly polarized (CP) EM beams. In a further example, the outer edge of dielectric layer 1612 can be wrapped with conductive foil and spaced from patch 1620, thereby forming an edge conductor, reducing surface mode excitation and increasing antenna gain. In some cases, it may be preferable to remove the shortening pin 1678 from the antenna 1600.

  In yet another variation illustrated in FIG. 18, one of the two SMA probes 1670 is removed (or not attached) and one stub 1628 and stripline 1624 that are substantially parallel to the remaining stub 1628 are not coupled. Thus, the antenna 1800 can be adapted to single mode operation when transmitting and receiving an EM beam.

(Very high gain antenna applications (direct broadcast satellite etc.))
19 to 20
Referring to FIGS. 19 and 20, reference numeral 1900 refers generally to a planar microstrip array antenna that implements features of the present invention for single mode operation such as beam transmission and reception. Antenna 1900 includes a substantially square dielectric layer 1912. The width 1902 and length 1903 of the layer 1912 may be equal or different and are determined by the number of patches used, described below, by a width and length 1902a of at least 0.50λ _ε beyond the outer edge of the patch 1920. It is preferable to extend.

Dielectric layer 1912 defines a bottom side 1912a to which conductive ground plane 1916 is coupled and an upper side 1912b to which an array of conductive radiating patches 1920 is coupled, and within dielectric layer 1912, patch 1920 and stripline 1924. A resonant cavity is formed between the ground plane 1916 and the ground plane 1916. The patch 1920 has a substantially square shape, has four corners 1920a and four radial edges 1920b, each having a length 1920c of about 0.50λ _ε . As seen in FIG. 19, patch 1920 electrically interconnects with an array of parallel vertical conductive striplines 1924 via one corner 1920a or two opposing corners 1920a, which is a horizontal conductive transmission line ( through a horizontal conductive transmission line) 1926. Strip line 1924 and transmission line 1926 are coupled to dielectric layer 1912. The patches 1920 are spaced apart by a vertical center-to-center distance 1960 that is preferably about 1λ _ε (as viewed in FIG. 19). The patches 1920 are preferably arranged in a plurality (as viewed in FIG. 19) vertical rows on the top surface 1912b, which are offset relative to each other above and below the horizontal transmission line 1926 in FIG. Illustrated as two (as viewed in FIG. 19) vertical rows 1928 (shown as dotted lines), each row comprising two patches 1920, for a total of 32 patches 1920 making up antenna 1900.

The width 1984 (FIG. 19) of each stripline 1924 is preferably determined assuming a characteristic impedance of about 50-200 ohms. Each transmission line 1926 includes a first portion 1926a, a second portion 1926b, and a third portion 1926c. Each first portion 1926a is preferably sized to have a characteristic impedance of about 100 ohms when the input impedance is about 50 ohms. The width and length of each second portion 1926b is determined by a quarter wavelength converter so that the incoming signal from the feed line is substantially transmitted. That is, the input impedance in the feeder line 1974 is appropriately matched. The width and length of each third portion 1926c of the transmission line 1926 are determined so that the traveling wave from the feed line 1974 is not reflected by the joints 1927a and 1927b. Therefore, the length of each third portion 1926c, in order to ensure that the closer to the phase difference 360 ° as possible of the traveling wave at the junction 1927a and 1927B, is preferably about 1 [lambda _epsilon. The width of each third portion 1926 c is preferably sized so that the characteristic impedance is about half the characteristic impedance of the stripline 1924.

  In order to obtain optimum performance at a particular frequency, the dimensions of the patch 1920, striplines 1924 and 1926, opening 1950, and center-to-center distance 1960 are higher order in the antenna cavity formed in the dielectric 1912. Standing waves are generated and are thus calculated individually so that the electric fields radiating from the radiating edge 1920b interfere with each other. The number of patches 1920 determines not only the overall size of the antenna 1900 but also its directivity. The level of the side lobe of the antenna 1900 is determined by the electric field distribution at the radiation edge 1920b. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and location of each patch 1920 and the feed scheme. To achieve high directivity, the electric field distribution between the radiating elements 1920 should be as uniform as possible. Dielectric layer 1912 has an electric field zero point. In some cases, antenna 1900 may include one or more shortened pins (not shown) that electrically connect ground planes, patches, and / or striplines to suppress unwanted mode excitation. Can do. The above calculations and analyzes have been performed, for example, on the cavity model described by Lee and Hsieh, and for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product-moment method described in software Ensemble® available from www.software-environment.com are used.

  A conventional SMA probe 1970 (FIG. 20) is provided for single mode operation such as beam transmission and reception. The SMA probe 1970 is electrically connected to an outer conductor 1972 electrically connected to the ground plane 1916 and a transmission line 1926 between the portions 1926a to deliver EM energy to and / or from the antenna 1900. , Including an inner (or feed) conductor 1974 centered along it, to optimize the impedance matching and appropriate radiation pattern of the antenna 1900. The probe 1970 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 1974 and the center patch 1922 to maintain contact therebetween, with the SMA probe 1970 passing through the ground plane 1916. In this case, an appropriate seal (not shown) can be provided to hermetically seal the connecting portion. It is understood that the other end of the SMA probe 1970 that is not connected to the antenna 1900 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want to be.

  In operation, antenna 1900 can be used to transmit and receive linearly polarized (LP) EM beams. During transmission of the EM beam, an incoming signal from the SMA probe 1970 travels as a traveling wave through the first portion 1926a along the transmission line 1926, where the first portion is a quarter wavelength converter. EM power is transmitted with minimal reflection to the two branches 1926b and 1926c and to the four striplines 1924 at each branch 1926b and 1926c. EM power is transmitted through stripline 1924 to the array of patches 1920. Next, the patch 1920 and a portion of the stripline 1924 induce higher order standing waves due to proper radiation through the opening 1950 of the antenna 1900.

  It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the signal transmission antenna 1900 is mutually the same as the signal reception antenna operation. Thus, for example, antenna 1900 can be positioned in a home and oriented to receive a beam carrying television signals in a given frequency band or channel from a stationary or equatorial satellite. The antenna 1900 is thus oriented by directing the top surface 1912b toward the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 1900 are appropriately sized to receive the beam, the beam passes through aperture 1950 to induce a higher order standing wave, which forms in dielectric layer 1912. The EM power is passed to the SMA probe 1970 through the strip line 1924 and the transmission line 1926. Next, EM power is passed from the SMA probe 1970 through a cable (not shown) and sent to a receiver such as a decoder (not shown).

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 19 and 20 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 1920 can be provided to narrow the beam, or the number of patches 1920 used can be reduced to reduce the physical space required for the antenna 1900 of the present invention.

21 to 22
Referring to FIGS. 21 and 22, reference numeral 2100 refers generally to a planar microstrip array antenna that implements features of the present invention for single mode operation such as transmitting and receiving beams. Antenna 2100 includes a substantially square dielectric layer 2112. The width 2102 and length 2103 (FIG. 21) of the layer 2112 is determined by the number of patches used, as described below, and is at least 0.50λ _ε wide and long beyond the outer edges of the patch 2120 and stripline 2126. Preferably it extends by 2102a.

The dielectric layer 2112 defines a bottom side 2112a to which a conductive ground plane 2116 is coupled and an upper side 2112b to which an array of conductive radiating patches 2120 is coupled, and within the dielectric layer 2112 the patch 2120 and stripline 2124. And a ground plane 2116 to form a resonant cavity. Patch 2120 is in the form of generally square, having four corners 2120a and four radiating edges 2120b, each having a length 2120c of about 0.50λ _ε. Patch 2120 is electrically interconnected with one of an array of four conductive striplines 2124 via one corner 2120a, which is electrically interconnected via conductive stripline 2126. Strip line 2124 and transmission line 2126 are coupled to dielectric layer 2112. Patch 2120 is preferably (as viewed in FIG. 21) of about 1 [lambda _epsilon by a vertical center-to-center distance 2160 spaced. The patch 2120 is preferably arranged in a plurality of eight rows on the top surface 2112b, which is typically illustrated in FIG. 21 by rows 2114 and 2116, each row comprising four patches 2120 for a total of 32 The individual patches 2120 constitute the antenna 2100. The width of each strip line 2124 is preferably determined on the assumption that the characteristic impedance is about 50-200 ohms. Each transmission line 2126 includes a first portion 2126a that is preferably configured to have a characteristic impedance of about 100 ohms with an input impedance of about 50 ohms, the feed line being described below with respect to the SMA probe 2170. So that it is centered on the stripline 2126 to ensure proper radiation. Each transmission line 2126 further includes a second portion 2126b that is preferably configured as a quarter wavelength converter to have minimal reflection at the junction with the stripline 2124.

  In order to obtain optimum performance at a particular frequency, the dimensions of the patch 2120, striplines 2124 and 2126, opening 2150, and center-to-center distance 2160 are higher order in the antenna cavity formed in the dielectric 2112. Standing waves are generated and are thus calculated individually so that the electric fields radiating from the radiating edge 2120a intensify and interfere with each other. The number of patches 2120 determines not only the overall size of the antenna 2100 but also its directivity. The level of the side lobe of the antenna 2100 is determined by the electric field distribution between the radiating elements 2120. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and location of each patch 2120 and the feed scheme. To achieve high directivity, the electric field distribution between the radiating elements 2120 should be as uniform as possible. Dielectric layer 2112 has a field zero point in patch 2120 and connecting stripline 2124. In some cases, antenna 2100 may include one or more shortened pins (not shown) that electrically connect ground planes, patches, and / or striplines to suppress undesirable mode excitation. Can do. The above calculations and analyzes are performed, for example, in the cavity model described by Lee and Hsieh, and in, for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product-moment method described in software Ensemble® available from www.software-environment.com are used.

  A conventional SMA probe 2170 (FIG. 22) is provided for single mode operation such as beam transmission and reception. Each SMA probe 2170 is electrically connected to the transmission line 2126 between the outer conductor 2172 electrically connected to the ground plane 2116 and between the portions 2126a and 2126b for delivering EM energy to and / or from the antenna 2100. Connected to and centrally disposed along the center (or feed) conductor 2174 to optimize the impedance matching of the antenna 2100 to induce centrally-peaked radiation. The probe 2170 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 2174 and the center stripline 2126 to maintain contact therebetween, and the SMA probe 2170 provides a ground plane 2116. When passing, an appropriate seal (not shown) can be provided to hermetically seal the connection. It is understood that the other end of the SMA probe 2170 that is not connected to the antenna 2100 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder used for television signals. I want to be.

  In operation, the antenna 2100 can be used to transmit and receive linearly polarized (LP) EM beams. During transmission of the EM beam, the incoming signal from the SMA probe 2170 travels as a traveling wave along the transmission line 2126 through the first portion 2126a and the second portion 2126b, which serves as a quarter wavelength converter. Acts and transmits EM power to the four striplines 2124 with minimal reflection. EM power is transmitted through stripline 2124 to an array of patches 2120. The patch 2120 then induces a higher order standing wave because the radiation through the aperture 2150 of the antenna 2100 is appropriate.

  It is well known that antennas transmit and receive signals to each other. Accordingly, it can be understood that the operation of the antenna 2100 for signal transmission is mutually the same as the antenna operation for signal reception. Thus, for example, antenna 2100 can be positioned in a home and oriented to receive a beam carrying television signals in a given frequency band or channel from a stationary or equatorial satellite. The antenna 2100 is thus oriented by directing the upper surface 2112b to the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 2100 are sized appropriately to receive the beam, the beam passes through aperture 2150 and induces a standing wave that resonates within dielectric layer 2112. Standing waves induced in a resonant cavity defined in dielectric layer 2112 are transmitted through stripline 2124, transmission line 2126 and SMA probe 2170 and transmitted to a receiver such as a decoder (not shown). .

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 21 and 22 are intended to illustrate rather than to limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 2120 can be provided to narrow the beam, or the number of patches 2120 used can be reduced to reduce the physical space required for the antenna 2100 of the present invention.

23 to 24
Referring to FIGS. 23 and 24, reference numeral 2300 refers generally to a planar microstrip array antenna that implements features of the present invention for dual mode operation such as beam transmission and reception. Antenna 2300 includes a substantially square dielectric layer 2312. The width 2302 and length 2303 (FIG. 23) of the layer 2312 is determined by the number of patches used, as described below, and is at least 0.50λ _ε beyond the outer edges of the patches 2320 and transmission lines 2325 and 2327 and It is preferable to extend the length 2302a.

Dielectric layer 2312 defines a bottom side 2312a to which a conductive ground plane 2316 is coupled and an upper side 2312b to which an array of conductive radiating patches 2320 is coupled, and within dielectric layer 2312, patch 2320 and stripline 2324. And a resonant cavity is formed between 2326 and the ground plane 2316. Patch 2320 is substantially square in shape, has four corners 2320a and four radial edges 2320b, each having a length 2320c of about 0.50λ _ε . As seen in FIG. 23, the patch 2320 is electrically interconnected through two adjacent corners 2320a, one of the adjacent corners being electrically connected to one of the array of eight vertical conductive striplines 2324; The other adjacent corner is electrically connected to one of an array of eight horizontal conductive striplines 2326. The vertical stripline 2324 is electrically interconnected via a horizontal conductive transmission line 2325 and the horizontal stripline 2326 is electrically interconnected via a vertical conductive transmission line 2327. Strip lines 2324 and 2326 and transmission lines 2325 and 2327 are coupled to dielectric layer 2312. The patches 2320 are preferably separated by a center-to-center distance 2360 of about 1λ _ε . The patch 2320 is preferably arranged in a plurality of rows and columns on the top surface 2312b, which is typically illustrated in FIG. 23 by rows 2328 and columns 2329, each row and column comprising four patches 2320, A total of 32 patches 2320 constitute the antenna 2300. The width of each stripline 2324 is preferably determined assuming a characteristic impedance of about 50-200 ohms. Each transmission line 2325 and 2327 includes first portions 2326a and 2326a that are preferably configured to have a characteristic impedance of about 100 ohms with an input impedance of about 50 ohms, the feed line being described below with respect to SMA probe 2370. So that it is centered on the stripline 2325 to ensure proper radiation. Each transmission line 2325 and 2327 further includes a second portion 2325b and 2327b that is preferably configured as a quarter-wavelength converter to have minimal reflection at the junction with striplines 2324 and 2326.

  In order to obtain optimum performance at a particular frequency, the dimensions of the patch 2320, striplines 2324 and 2326, opening 2350, and center-to-center distance 2360 are higher order in the antenna cavity formed in the dielectric 2312. Standing waves are generated and are thus calculated individually so that the electric fields radiating from the radiating edge 2320b intensify and interfere with each other.

  The number of patches 2320 determines not only the overall size of the antenna 2300 but also its directivity. The level of the side lobe of the antenna 2300 is determined by the electric field distribution between the radiating elements 2320. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and location of each patch 2320 and the feed scheme. To achieve high directivity, the electric field distribution between the radiating elements 2320 should be as uniform as possible. Dielectric layer 2312 has an electric field zero point between one ground plane 2316 and the other patch 2320 and striplines 2324 and 2326. In some cases, antenna 2300 may include one or more shortened pins (not shown) that electrically connect ground planes, patches, and / or striplines to suppress unwanted mode excitation. Can do. The above calculations and analyzes are performed, for example, in the cavity model described by Lee and Hsieh, and in, for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product-moment method described in software Ensemble® available from www.software-environment.com are used.

  Two conventional SMA probes 2370 (FIG. 24) are provided for dual mode operation such as beam transmission and reception. Each SMA probe 2370 is electrically connected to an outer conductor 2372 electrically connected to a ground plane 2316 and transmission lines 2325 and 2327 for delivering EM energy to and / or from the antenna 2300. , And an inner (or feed) conductor 2374 centered along it, to optimize the impedance matching and radiation efficiency of the antenna 2300. The probe 2370 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 2374 and each transmission line 2325 and 2327 to maintain contact between them, and the SMA probe 2370 is connected to the ground plane. When passing through 2316, an appropriate seal (not shown) can be provided to hermetically seal the connection. It is understood that the other end of the SMA probe 2370 that is not connected to the antenna 2300 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want to be.

  In operation, the antenna 2300 can be used to transmit and receive linearly polarized (LP) EM beams. During transmission of the EM beam exemplified by the signal from the SMA probe 2370 to the transmission line 2325, the incoming signal travels as a traveling wave along the transmission line 2325 through the first portion 2325a and the second portion 2325b, Acts as a quarter wave converter and transmits EM power to the four striplines 2324 with minimal reflection. EM power is transmitted through stripline 2324 to an array of patches 2320. The patch 2320 then induces a higher order standing wave because the radiation through the aperture 2350 of the antenna 2300 is appropriate.

  Within antenna 2300, the vertical mode excitation is orthogonal to that of the horizontal mode, so crosstalk between the two input signals is minimized. That is, two orthogonal vertical and horizontal modes can be excited separately.

  It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the antenna 2300 for signal transmission is mutually the same as the antenna operation for signal reception. Thus, for example, antenna 2300 can be positioned in a home and oriented to receive a beam carrying television signals in a predetermined frequency band or channel from a stationary or equatorial satellite. The antenna 2300 is thus oriented by directing the top surface 2312b toward the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 2300 are sized appropriately to receive the beam, the beam passes through aperture 2350 and induces a standing wave that resonates within dielectric layer 2312. Standing waves induced in a resonant cavity defined in dielectric layer 2312 are transmitted to SMA probe 2370 through stripline 2324 and transmission line 2325 and / or through stripline 2326 and transmission line 2327 to the decoder. (Not shown) or the like. It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the antenna 2300 for signal transmission is mutually the same as the antenna operation for signal reception. Therefore, signal transmission by antenna 2300 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 23 and 24 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 2320 can be provided to narrow the beam, or the number of patches 2320 used can be reduced to reduce the physical space required for the antenna 2300 of the present invention. With proper modification near the feeding area, two orthogonal circularly polarized (CP) dual mode operation can be achieved.

25 to 26
Referring to FIGS. 25 and 26, reference numeral 2500 refers generally to a planar microstrip array antenna that implements features of the present invention for single mode operation such as transmitting and receiving beams. Antenna 2500 includes a generally square dielectric layer 2512. The width 2502 and length 2503 of the layer 2512 may be equal or different and are determined by the number of patches used as described below and are at least 0.50λ _ε in width and length beyond the outer edge of the patch 2520. It is preferable to extend by 2502a.

Dielectric layer 2512 defines a bottom side 2512a to which conductive ground plane 2516 is coupled and an upper side 2512b to which an array of conductive radiating patches 2520 is coupled, and within dielectric layer 2512, ground plane 2516 and patch 2520. And a resonant line is formed between the line and the strip line 2524. Patch 2520 is in the form of generally square, having four corners 2520a and four radiating edges 2520b, each having a length 2520c of about 0.50λ _ε. As seen in FIG. 25, patch 2520 is electrically interconnected to an array of substantially parallel vertical conductive striplines 2524 via one corner 2520a or two opposing corners 2520a, which is substantially horizontal. The electrically conductive transmission line 2526 is electrically interconnected, and the strip line 2524 and the transmission line 2526 are coupled to the dielectric layer 2512. Patches 2520 are spaced apart by a longitudinal center-to-center distance 2560 (as viewed in FIG. 25) of preferably about 1λ _ε . The patches 2520 are preferably arranged in a plurality of columns (as viewed in FIG. 25) above and below the transmission line 2526, typically represented by a row 2528 illustrated by dotted lines. . The width of each strip line 2524 is preferably determined on the assumption that the characteristic impedance is about 50-200 ohms. Transmission line 2526 includes a first portion 2526a that is preferably configured to have a characteristic impedance of about 100 ohms with an input impedance of about 50 ohms, the feed line being a transmission line as described below with respect to SMA probe 2570. Preferably centered on 2526 to ensure proper radiation. Transmission line 2526 further includes two second portions 2526b configured to have minimal reflection at the junction with stripline 2524.

  To obtain optimum performance at a particular frequency, the dimensions of the patch 2520, stripline 2524, transmission line 2526, aperture 2550, and center-to-center distance 2560 are higher order within the antenna cavity formed in the dielectric 2512. Standing waves are generated and are thus calculated individually so that the electric fields radiating from the radiating edge 2520b interfere with each other. The number of patches 2520 determines not only the overall size of the antenna 2500, but also its directivity. The level of the side lobe of the antenna 2500 is determined by the electric field distribution between the radiating elements 2520. Thus, antenna characteristics such as directivity and sidelobe levels are controlled by the size and location of each patch 2520 and the feed scheme. In order to achieve high directivity, the electric field distribution in the radiating element 2520 should be as uniform as possible. Dielectric layer 2512 has an electric field zero point in the vicinity of patch 2520 and stripline 2524. In some cases, antenna 2500 may include one or more shortened pins (not shown) that electrically connect ground planes, patches, and / or striplines to suppress unwanted mode excitation. Can do. The above calculations and analyzes have been performed, for example, on the cavity model described by Lee and Hsieh, and for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product-moment method described in software Ensemble® available from www.software-environment.com are used.

  A conventional SMA probe 2570 (FIG. 26) is provided for single mode operation such as beam transmission and reception. Each SMA probe 2570 is electrically connected to and centered along an outer conductor 2572 electrically connected to a ground plane 2516 and a transmission line 2526 for delivering EM energy to or from the antenna 2500. To optimize the impedance matching of the antenna 2500 and the aperture efficiency of the antenna. Probe 2570 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 2574 and the center stripline 2526a to maintain contact therebetween, and the SMA probe 2570 can be connected to the ground plane 2516. When passing, an appropriate seal (not shown) can be provided to hermetically seal the connection. Understand that the other end of the SMA probe 2570 that is not connected to the antenna 2500 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want to be.

  In operation, the antenna 2500 can be used to transmit and receive linearly polarized (LP) EM beams. During transmission of an EM beam, exemplified by a signal from the SMA probe 2570 to the transmission line 2526, the incoming signal travels as a traveling wave through the first portion 2526a along the transmission line 2526, causing the EM power to pass through the two branches 2526b. And then to the stripline 2524 with minimal reflection. EM power is transmitted through stripline 2524 to the array of patches 2520. The patch 2520 then induces a higher order standing wave because the radiation through the opening 2550 of the antenna 2500 is appropriate.

  It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the signal transmission antenna 2500 is mutually the same as the signal reception antenna operation. Thus, for example, antenna 2500 can be positioned in a home and oriented to receive a beam carrying television signals in a given frequency band or channel from a stationary or equatorial satellite. The antenna 2500 is thus oriented by directing the top surface 2512b towards the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 2500 are appropriately sized to receive the beam, the beam passes through aperture 2550 and induces a standing wave, which is the patch 2520 in dielectric layer 2512. Resonates within the resonant cavity of the array. Standing waves induced in a resonant cavity defined in dielectric layer 2512 leak EM power through a transmission line network comprising striplines 2524 and 2526 to SMA probe 2570, such as a decoder (not shown), etc. To the receiver. It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the signal transmission antenna 2500 is mutually the same as the signal reception antenna operation. Therefore, signal transmission by antenna 2500 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 25 and 26 are intended to illustrate rather than to limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 2520 can be provided to narrow the beam, or the number of patches 2520 used can be reduced to reduce the physical space required for the antenna 2500 of the present invention.

27-28
Referring to FIGS. 27 and 28, reference numeral 2700 refers generally to a planar microstrip array antenna that implements features of the present invention for single mode operation such as beam transmission and reception. Antenna 2700 includes a substantially square dielectric layer 2712. The width 2702 and length 2703 of the layer 2712 may be equal or different and are determined by the number of patches used as described below and are at least 0.50λ _ε in width and length beyond the outer edge of the patch 2720. Preferably it extends by 2702a.

  Referring to FIG. 28, the dielectric layer 2712 defines a bottom layer 2712a to which a conductive ground plane 2716 is coupled and an upper side 2712b to which an array of conductive radiating patches 2720 (FIG. 27) is coupled. Within 2712, a resonant cavity is formed between the ground plane, patch 2720, and stripline 2724.

Returning to FIG. 27, the patch 2720 has a generally square shape and has four corners 2720a and four radial edges 2720b, each having a length 2720c of approximately 0.5λ _ε . As seen in FIG. 27, the patch 2720 is electrically interconnected to substantially horizontal and vertical conductive striplines 2724 via two, three or four corners 2720a, which are substantially horizontal conductive. They are electrically interconnected via transmission line 2726. Strip line 2724 and transmission line 2726 are coupled to dielectric layer 2712. The width of each stripline 2724 is preferably determined assuming a characteristic impedance of about 50-200 ohms. The transmission line 2726 includes a first portion 2726a that is preferably configured to have a characteristic impedance of about 100 ohms with an input impedance of about 50 ohms, and the feed line 2774 transmits as described below with respect to the SMA probe 2770. Positioned in the center on line 2726 to ensure proper radiation. Transmission line 2726 further includes two second portions 2726b that are preferably configured as quarter-wave converters to have minimal reflection. The signal from 2726b then travels through an additional quarter wavelength converter so that the power through vertical transmission line 2724 is evenly distributed between each other.

  To obtain optimum performance at a particular frequency, the dimensions of the patch 2720, stripline 2724 and transmission line 2726, opening 2750, and center-to-center distance 2760 are higher order within the antenna cavity formed in the dielectric 2712. Standing waves are generated and are thus individually calculated so that the electric fields radiating from the radiating edge 2720b interfere with each other.

  The number of patches 2720 determines not only the overall size of the antenna 2700 but also its directivity. The level of the side lobe of the antenna 2700 is determined by the electric field distribution at the radiating edge 2720b. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and location of each patch 2720 and the feed scheme. To achieve high directivity, the electric field distribution between the radiating elements 2720 should be as uniform as possible. Dielectric layer 2712 has an electric field zero point in the vicinity of patch 2720 and stripline 2724. In some cases, antenna 2700 may include one or more shortened pins (not shown) that electrically connect ground planes, patches, and / or striplines to suppress unwanted mode excitation. Can do. The above calculations and analyzes have been performed, for example, on the cavity model described by Lee and Hsieh, and for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product-moment method described in software Ensemble® available from www.software-environment.com are used.

  A conventional SMA probe 2770 (FIG. 28) is provided for single mode operation such as beam transmission and reception. The SMA probe 2770 is electrically connected to an outer conductor 2772 that is electrically connected to a ground plane 2716 to transmit EM energy to or from the antenna 2700, and a transmission line 2726 for appropriate radiation. , Including an inner (or feed) conductor 2774 disposed centrally therewith. Probe 2770 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 2774 and the center stripline 2726a to maintain contact between them, and the SMA probe 2770 can connect the ground plane 2716 When passing, an appropriate seal (not shown) can be provided to hermetically seal the connection. It is understood that the other end of the SMA probe 2770 that is not connected to the antenna 2700 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want to be.

  In operation, the antenna 2700 can be used to transmit and receive linearly polarized (LP) EM beams. During transmission of an EM beam, exemplified by the signal from the SMA probe 2770 to the transmission line 2726, the incoming signal is transmitted along the transmission line 2726 with minimal reflection and a relatively uniform power distribution between the vertical striplines 2724. The first part 2726a travels as a traveling wave through a second part 2726b that behaves as a quarter wavelength converter, and then passes through a quarter wavelength converter and a power divider to provide EM power. Is finally sent to the stripline 2724. EM power is transmitted through stripline 2724 to an array of patches 2720. The patch 2720 then induces a higher order standing wave through the radiating edge 2720 of each patch 2720 of the antenna 2700 for proper radiation.

  It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the antenna 2700 for signal transmission is mutually the same as the antenna operation for signal reception. Thus, for example, antenna 2700 can be positioned in a home and oriented to receive a beam carrying television signals in a given frequency band or channel from a stationary or equatorial satellite. The antenna 2700 is thus oriented by directing the top surface 2712b towards the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 2700 are sized appropriately to receive the beam, the beam passes through aperture 2750 to induce a standing wave, which is the patch 2720 in dielectric layer 2712. Resonates within the resonant cavity of the array. Standing waves induced in a resonant cavity defined in dielectric layer 2712 leak EM power through a transmission line network comprising striplines 2724 and 2726 to SMA probe 2770 and a decoder (not shown). ) And other receivers. It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the antenna 2700 for signal transmission is mutually the same as the antenna operation for signal reception. Therefore, signal transmission by antenna 2700 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 27 and 28 are intended to illustrate rather than to limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 2720 can be provided to narrow the beam, or the number of patches 2720 used can be reduced to reduce the physical space required for the antenna 2700 of the present invention.

29 to 31
Referring to FIGS. 29A and 29B (hereinafter “FIG. 29”) and FIG. 30, reference numeral 2900 is a planar microstrip that implements features of the present invention for dual mode operation such as beam transmission and reception. -Refers to the entire array antenna. Antenna 2900 includes a substantially square dielectric layer 2912. The width 2902 and length 2903 of the layer 2912 may be equal or different and are determined by the number of patches used as described below and are at least 0.50λ _ε in width and length beyond the outer edge of the patch 2920. Preferably it extends by 2902a.

  Referring to FIG. 30, dielectric layer 2912 defines a bottom side 2912a to which a conductive ground plane 2916 is coupled and an upper side 2912b to which an array of conductive radiating patches 2920 (FIG. 29) is coupled to form a dielectric layer. Within 2912, a resonant cavity is formed between ground plane 2916, patch 2920, and stripline 2924.

Returning to FIG. 29, the patch 2920 has a generally square shape and has four corners 2920a and four radial edges 2920b, each having a length 2920c of approximately 0.50λ _ε . As seen in FIG. 29, the patch 2920 is electrically interconnected to an array of substantially horizontal and vertical conductive striplines 2924 via two, three or four corners 2920a, which is a dielectric layer 2912. Combined with Stripline 2924 is electrically interconnected via a substantially horizontal conductive transmission line 2926 and a substantially vertical conductive transmission line 2928. Transmission lines 2926 and 2928 are coupled to dielectric layer 2912 and the intersection of transmission lines 2926 and 298 is indicated in FIG. 29 by dotted outline 2927 and is further described below with respect to FIG. The width of each stripline 2924 is preferably determined assuming a characteristic impedance of about 50-200 ohms. Transmission lines 2926 and 2928 include first portions 2926a and 2928a, respectively, preferably configured to have a characteristic impedance of about 100 ohms with an input impedance of about 50 ohms, and feed line 2974 is described below with respect to SMA probe 2970. Positioned on each transmission line 2926 and 2928 as described to ensure proper radiation. Each transmission line 2926 and 2928 further includes two second portions 2926b and 2928b, respectively, which are preferably configured as quarter wave converters to have minimal reflection.

  FIG. 30 shows one preferred configuration in which transmission lines 2926 and 2928 can intersect at dotted outline 2927 without electrical contact. Thus, as seen in FIG. 30, the transmission line 2928 includes a bridge with two vias 2928c that pass under the transmission line 2926 by the vias, and the two vias 2928c are in electrical contact with the ground plane 2916. Without passing through the opening of the ground plane 2916 and electrically connected by a microstrip 2928d (FIG. 31) that is electrically insulated from the ground plane 2916 via the dielectric 2913. In an alternative embodiment, a non-conductive intersection of transmission lines 2926 and 2928 is achieved by using a directional coupler described below with respect to FIGS.

  In order to obtain optimum performance at a particular frequency, the dimensions of the patch 2920, transmission lines 2924 and 2926, the opening 2950, and the center-to-center distance 2960 are higher order in the antenna cavity formed in the dielectric 2912. Standing waves are generated and are thus calculated individually so that the electric fields radiating from the radiating edge 2920b interfere with each other.

  The number of patches 2920 determines not only the overall size of the antenna 2900 but also its directivity. The level of the side lobe of the antenna 2900 is determined by the electric field distribution between the radiating elements 2920. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and location of each patch 2920 and the feed scheme. In order to achieve high directivity, the electric field distribution between the radiating elements 2920 should be as uniform as possible. Dielectric layer 2912 has an electric field zero point in the vicinity of patch 2920 and stripline 2924. In some cases, antenna 2900 may include one or more shortened pins (not shown) that electrically connect ground planes, patches, and / or striplines to suppress undesirable mode excitation. Can do. The above calculations and analyzes have been performed, for example, on the cavity model described by Lee and Hsieh, and for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product-moment method described in software Ensemble® available from www.software-environment.com are used.

Two conventional SMA probes 2970 (FIG. 30) are provided for dual mode operation such as beam transmission and reception. Each SMA probe 2970 is electrically connected to and along external conductors 2972 and transmission lines 2926 and 2928 that are electrically connected to ground plane 2916 for delivering EM energy to or from antenna 2900. Internal (or feed) conductor 2974 to optimize the impedance matching of antenna 2900. Feed line 2974, as shown in dotted outline 2927 (Fig. 29), from where the transmission line 2926 and 2928 intersect, off-center distance 2975 plus a multiple of lambda _epsilon about 1/4 wavelength It is preferable to place them apart. The probe 2970 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the feed line 2974 and the center stripline 2926a and maintain contact therebetween, with the SMA probe 2970 connecting the ground plane 2916. When passing, an appropriate seal (not shown) can be provided to hermetically seal the connection. It is understood that the other end of the SMA probe 2970 not connected to the antenna 2900 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want to be.

  In operation, the antenna 2900 can be used to transmit and receive linearly polarized (LP) EM beams. Upon transmission of an EM beam, exemplified by signals from SMA probe 2970 to transmission lines 2926 and 2928, the incoming signal passes through first portions 2926a and 2928a along transmission lines 2926 and 2928, respectively, with minimal reflection. Proceeding as a traveling wave, EM power is transmitted to the two branches 2926b and 2928b and then to the stripline 2924. EM power is transmitted through stripline 2924 to the array of patches 2920. The patch 2920 and a portion of the stripline 2924 then induce higher order standing waves through the aperture 2950 of the antenna 2900 for proper radiation.

  Within antenna 2900, the vertical mode excitation is orthogonal to that of the horizontal mode, so crosstalk between the two input signals is minimized. That is, two orthogonal vertical and horizontal modes can be excited separately.

  It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the antenna 2900 for signal transmission is mutually the same as the antenna operation for signal reception. Thus, for example, antenna 2900 can be positioned in a home and oriented to receive a beam carrying television signals in a given frequency band or channel from a stationary or equatorial satellite. The antenna 2900 is thus oriented by directing the top surface 2912b towards the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 2900 are sized appropriately to receive the beam, the beam passes through aperture 2950 and induces a standing wave, which is in a resonant cavity in dielectric layer 2912. Thus, resonance occurs between the array of patches 2920, the stripline 2924, and the ground plane 2916. Standing waves induced in a resonant cavity defined in dielectric layer 2912 are transmitted to SMA probe 2970 through a transmission line network comprising striplines 2924 and 2926, such as a decoder (not shown). Sent to the receiver. It is well known that antennas transmit and receive signals to each other. Therefore, it can be understood that the operation of the antenna 2900 for signal transmission is mutually the same as the antenna operation for signal reception. Therefore, signal transmission by antenna 2900 will not be further described here.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 29 and 30 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 2920 can be provided to narrow the beam, or the number of patches 2920 used can be reduced to reduce the physical space required for the antenna 2900 of the present invention. With proper modification near the feeding area, two orthogonal circularly polarized (CP) dual mode operation can be achieved.

32 to 33
Referring to FIGS. 32 and 33, reference numeral 3200 refers to the entirety of a planar microstrip array antenna that implements features of the present invention for dual mode operation such as transmitting and receiving beams. Antenna 3200 includes a substantially square dielectric layer 3212. The width 3202 and length 3203 (FIG. 32) of the layer 3212 may be equal or different and are determined by the number of patches used, as described below, and at least 0.50λ _ε beyond the outer edge of the patch 3220. It preferably extends by a width and length 3202a.

Referring to FIG. 33, the dielectric layer 3212 defines a bottom side 3212a to which a conductive ground plane 3216 is coupled and an upper side 3212b to which an array of conductive radiating patches 3220 are coupled, and within the dielectric layer 3212, A resonant cavity is formed between patch 3220, striplines 3224 and 3226, and ground plane 3216. Referring to FIG. 32, the patch 3220 has a generally square shape and has four corners 3220a and four radial edges 3220b, each having a length 3220c of approximately 0.50λ _ε . As seen in FIG. 32, the patch 3220 is electrically interconnected to an array of substantially vertical conductive striplines 3224 and horizontal conductive striplines 3226 via corners 3220a. Striplines 3224 and 3226 are electrically interconnected to directional coupling 3400, described in more detail below with respect to FIG. 34, via individual transmission lines 3224a, 3224b, 3226a and 3226b, and SMA probes. Communicate the probe and EM energy as described in more detail with respect to 3270. Striplines 3224, 3226 and transmission lines 3224a, 3224b, 3226a, and 3226b are coupled to dielectric layer 3212. The patches 3220 are preferably separated by a center-to-center distance 3260 of about 1λ _ε . The patch 3220 is preferably arranged in four subarrays, with each subarray having a plurality of columns and rows on the top surface 3212b, which are outlined in dotted lines by subarrays 3222 having rows 3228 and columns 3229 offset from each other. Typically exemplified. The width of each stripline 3224 and 3226 is preferably determined assuming a characteristic impedance of about 50-200 ohms. Transmission lines 3224a and 3226b are preferably configured to have a characteristic impedance of about 100 ohms with an input impedance of about 50 ohms, and feed lines are on striplines 3224 and 3226 as described below with respect to SMA probe 3270. Position and ensure proper phase of each stripline and patch for optimal gain results. Transmission lines 3224b and 3226b are preferably configured as two quarter wavelength converters in series so as to have minimal reflection.

  To obtain optimum performance at a particular frequency, the dimensions of the patch 3220, striplines 3224, 3226 and opening 3250, center-to-center distance 3260, coupler 3100 are higher order within the antenna cavity formed in the dielectric 3212. Standing waves are generated, and are thus calculated individually so that the electric fields radiating from the radiating edge 3220b interfere with each other.

  The number of patches 3220 determines not only the overall size of the antenna 3200 but also its directivity. The level of the side lobe of the antenna 3200 is determined by the electric field distribution between the radiating elements 3220. Thus, antenna characteristics such as directivity and sidelobe level are controlled by the size and location of each patch 3220 and the feed scheme. To achieve high directivity, the electric field distribution between the radiating elements 3220 should be as uniform as possible. Dielectric layer 3212 has a field zero point in patch 3220 and striplines 3224 and 3226. In some cases, antenna 3200 may include one or more shortened pins (not shown) that electrically connect ground planes, patches and / or striplines to suppress unwanted mode excitation. Can do. The above calculations and analyzes have been performed, for example, on the cavity model described by Lee and Hsieh, and for example, Anasoft Corp. Will not be described in further detail here, since techniques such as the product-moment method described in software Ensemble® available from www.software-environment.com are used.

  Two conventional SMA probes 3270 (only one shown in FIG. 33) are provided for dual mode operation such as beam transmission and reception. Each SMA probe 3270 is electrically connected to an outer conductor 3272 electrically connected to a ground plane 3216 and to an individual transmission line 3224a or 3226a for delivering EM energy to and / or from the antenna 3200. And includes an inner (or feed) conductor 3274 disposed along it to ensure the proper phase of each stripline and patch for optimal gain results. Probe 3270 is preferably an SMA probe, but any suitable coaxial probe and / or connection configuration can be used to implement the connection. For example, a conductive adhesive (not shown) can be used to couple between the inner conductor 3274 and the transmission line 3224a to maintain contact therebetween, with the SMA probe 3270 passing through the ground plane 3216. When doing so, an appropriate seal | sticker (not shown) can be provided and a connection part can be airtightly sealed. It is understood that the other end of the SMA probe 3270 that is not connected to the antenna 3200 can be connected via a cable (not shown) to a signal generator or receiver such as a satellite signal decoder for use with television signals. I want to be.

  In operation, antenna 3200 can be used to transmit and receive linearly polarized (LP) EM beams. When transmitting an EM beam exemplified by using a signal from the SMA probe 3270 to the transmission line 3224a using the feed line, the incoming signal passes through the coupler 3400 along the transmission line 3224a and is opposed to the transmission line 3224a. It proceeds as a traveling wave that reaches 3224a. The transmission line 3224a sends the EM power of the signal to the two branch transmission lines 3224b with subsequent minimal reflection to the strip line 3224 of each branch transmission line 3224b. EM power is transmitted through stripline 3224 to an array of patches 3220. Next, the patch 3220 and a portion of the stripline 3224 induce higher order standing waves because the radiation through the aperture 3250 of the antenna 3200 is adequate.

  When transmitting an EM beam exemplified by using a signal from the SMA probe 3270 to the transmission line 3226a using the feed line, the incoming signal passes through the coupler 3400 along the transmission line 3226a and is opposed to the transmission line 3226a. It proceeds as a traveling wave that reaches 3226a. Transmission line 3226a sends the EM power of the signal with minimal reflection to the two branch transmission lines 3226b and then to the strip line 3226 of each branch transmission line 3226b. EM power is transmitted through stripline 3226 to the array of patches 3220. The patch 3220 then induces a higher order standing wave for proper radiation through the aperture 3250 of the antenna 3200.

  Within the antenna 3200, the vertical mode excitation is orthogonal to that of the horizontal mode, so crosstalk between the two input signals is minimized. That is, two orthogonal vertical and horizontal modes can be excited separately.

  It is well known that antennas transmit and receive signals to each other. Accordingly, it can be understood that the operation of the antenna 3200 for signal transmission is mutually the same as the antenna operation for signal reception. Thus, for example, antenna 3200 can be positioned in a home and oriented to receive a beam carrying television signals in a given frequency band or channel from a stationary or equatorial satellite. The antenna 3200 is thus oriented by directing the top surface 3212b toward the beam source so that it is substantially perpendicular to the direction of the beam. Assuming that the elements of antenna 3200 are sized appropriately to receive the beam, the beam passes through aperture 3250 and induces a standing wave that resonates within dielectric layer 3212. Standing waves induced in a resonant cavity defined in dielectric layer 3212 leak electromagnetic force through striplines 3224 and 3226 and coupler 3400 to an appropriate SMA probe 3270, such as a decoder (not shown). To the receiver.

  It should be understood that the present invention can take many forms and embodiments. The embodiments described with respect to FIGS. 32 and 33 are intended to illustrate rather than limit the invention. Accordingly, several variations are possible in the above without departing from the spirit or scope of the invention. For example, additional patches 3220 can be provided to narrow the beam, or the number of patches 3220 used can be reduced to reduce the physical space required for the antenna 3200 of the present invention. With proper modification near the feeding area, two orthogonal circularly polarized (CP) dual mode operation can be achieved.

34 to 35
Referring to FIG. 34, reference numeral 3400 is for coupling two EM energy sources to two EM energy destinations so that EM energy can be communicated between the two sources and the two destinations without interference. Figure 1 shows an overall planar microstrip directional coupler embodying features of the present invention. As described above with respect to FIGS. 32-33, coupler 3400 is preferably incorporated into a microstrip antenna such as antenna 2900 and antenna 3200. However, the coupler 3400 can also function as a stand-alone coupler as shown in FIG. 34, and will be described as such herein for simplicity. Thus, coupler 3400 includes a substantially square dielectric layer 3412. The dielectric layer 3412 has a width 3402 and a length 3403 that may be equal or different.

Referring to FIG. 35, the dielectric layer 3412 includes a bottom side 3412a that can optionally couple a conductive ground plane 3416, and a top side 3412b to which an array of conductive striplines is coupled to form a directional coupler. Define. The stripline includes first striplines 3420 and 3422 that transmit EM energy and second striplines 3424 and 3426 that transmit EM energy. The width of each stripline 4124 is preferably a characteristic impedance _{Z 0} is determined assuming approximately 50 to 200 ohms.

Striplines 3420, 3422, 3424 and 3426 are connected to a substantially rectangular bridge 3430 that has two end portions 3432, an upper and lower portion 3434, and a central section portion 3432 as seen in FIG. The width of each end portion 3432 is determined assuming that the characteristic impedance Z ₀ is about 50-200 ohms, and the length 3432a of each end portion 3432 is preferably about 0.25λ _ε . The width of each upper and lower portions 3434 determines characteristic impedance _Z 0 / (2 square root) Assuming the approximately 35-141 ohms, the length 3434a of each half of each end portion 3432 is about 0.25 [lambda _epsilon It is preferable. Each upper and lower portion 3434 is further characterized by an end 3434b that is chamfered at an angle of about 45 ° with respect to the upper and lower portions. The width of the central section part 3436 is preferably a characteristic impedance _Z 0/2 is determined assuming approximately 25-100 ohms.

  In operation, when coupler 3400 is used with the antenna array of FIG. 29, a line such as line 2928a shown in FIG. 29 is connected to each first stripline 3420 and 3422, such as line 2926a shown in FIG. A line is connected to each first stripline 3424 and 3426. EM energy on stripline 2928a is passed from stripline 3420 to stripline 3422 (or from stripline 3422 to stripline 3420) with substantially negligible loss to striplines 3424 and 3426. Similarly, EM energy on stripline 2926a is passed from stripline 3424 to stripline 3426 (or from stripline 3426 to stripline 3424) with substantially negligible loss to striplines 3420 and 3422. .

  Any of the above antennas that are configured to operate at one frequency will have the desired dielectric constant for one frequency if the dielectric constant of the dielectric layer remains substantially the same at the desired frequency as at one frequency. By scaling the overall dimensions of the antenna in direct proportion to the frequency ratio, virtually any other desired without significantly changing features such as the radiation pattern and antenna efficiency at one frequency Can be reconfigured to operate at any frequency.

  While exemplary embodiments of the present invention have been illustrated and described, the foregoing disclosure contemplates a wide range of modifications, changes and substitutions, and in some cases without corresponding use of other features. Several features can be used. Accordingly, the appended claims are to be broadly construed in a manner consistent with the scope of the present invention, and the inductively provided reference numerals are provided by way of example for convenience and efficiency of description, and any claim in any sense It is appropriate to understand and interpret what is not limiting.

It is a perspective view of a planar array antenna. FIG. 2 is a longitudinal sectional view of the antenna of FIG. 1 taken along line 2-2 of FIG. FIG. 2 is a perspective view of an alternative embodiment of the planar array antenna of FIG. It is a top view of a planar array antenna. FIG. 5 is a longitudinal sectional view of the antenna of FIG. 4 taken along line 5-5 of FIG. It is a top view of a planar array antenna. FIG. 7 is a longitudinal sectional view of the antenna of FIG. 6 taken along line 7-7 of FIG. It is a top view of a planar array antenna. FIG. 9 is a longitudinal sectional view of the antenna of FIG. 8 taken along line 9-9 of FIG. It is a top view of a planar array antenna. FIG. 11 is a longitudinal sectional view of the antenna of FIG. 10 taken along line 11-11 of FIG. FIG. 12 is an enlarged view of a portion of the antenna of FIG. 11 depicting a boundary line with line 12 of FIG. It is a top view of a planar array antenna. FIG. 14 is a longitudinal sectional view of the antenna of FIG. 13 taken along line 14-14 of FIG. FIG. 14 is an enlarged view of a portion of the antenna of FIG. 13 with a boundary line drawn by line 15 of FIG. 13. It is a top view of a planar array antenna. FIG. 17 is a longitudinal cross-sectional view of the antenna of FIG. 16 taken along line 17-17 of FIG. FIG. 17 is a plan view of an alternative embodiment of the antenna of FIG. It is a top view of a planar array antenna. 20 is a longitudinal sectional view of the antenna of FIG. 19 taken along line 20-20 of FIG. It is a top view of a planar array antenna. FIG. 22 is a longitudinal sectional view of the antenna of FIG. 21 taken along line 22-22 of FIG. It is a top view of a planar array antenna. FIG. 24 is a longitudinal sectional view of the antenna of FIG. 23 taken along line 24-24 of FIG. It is a top view of a planar array antenna. FIG. 26 is a longitudinal cross-sectional view of the antenna of FIG. 25 taken along line 26-26 of FIG. It is a top view of a planar array antenna. FIG. 28 is a longitudinal cross-sectional view of the antenna of FIG. 27 taken along line 28-28 of FIG. 29A and 29B are plan views of a planar array antenna. FIG. 30 is a longitudinal cross-sectional view of the antenna of FIGS. 29A and 29B taken along line 30-30 of FIGS. 29A and 29B. It is a bottom view of the microstrip of the antenna of FIG. It is a top view of a planar array antenna. FIG. 33 is a longitudinal cross-sectional view of the antenna of FIG. 32 taken along line 33-33 of FIG. 2 is a plan view of a planar microstrip directional coupler that implements features of the present invention to couple two EM energy sources to two EM energy destinations. FIG. FIG. 35 is a longitudinal cross-sectional view of the coupler of FIG. 34 taken along line 35-35 of FIG.

Claims (50)

An antenna (100-3300),
A dielectric layer defining a first side and a second side;
A conductive ground plane disposed on the first side of the dielectric layer;
An array of radiating patches disposed and spaced apart on the second side of the dielectric layer;
An antenna comprising: at least one strip line disposed on the second side of the dielectric layer and electrically connected to at least one corner of each patch.   The antenna (100-3300) according to claim 1, wherein the patch and stripline are sized and positioned such that higher order standing waves are induced in the antenna in response to electromagnetic energy.   The antenna (100-3300) of claim 1, wherein the antenna is planar.   The at least one feeding means electrically connected to the ground plane, and at least one patch for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna. Antenna (100-1800).   A first conductive element electrically connected to the ground plane and electrically connected to at least one patch for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna; The antenna (100-1800) according to claim 1, further comprising at least one feeding means having a second conductive element.   Probe, SMA probe, aperture coupled line, and microstrip line electrically connected to at least one patch that feeds the ground plane and electromagnetic energy to the antenna and / or extracts electromagnetic energy from the antenna The antenna (100-1800) of claim 1, further comprising at least one of:   And further comprising at least two feeding means, each comprising one of a probe, an SMA probe, an aperture coupling line, and a microstrip line, each feeding means feeding the ground plane and electromagnetic energy to the antenna. The antenna (100-1800) of claim 1, wherein the antenna (100-1800) is diagonally electrically connected to at least one patch that extracts electromagnetic energy from the antenna.   The antenna (100-1300) of claim 1, wherein the patches are arranged in a square array of equal rows and columns.   The antenna of claim 1, further comprising at least one adjustment stub disposed on the second side of the dielectric layer and extending substantially perpendicularly from at least one of the at least one stripline. 100).   The patch includes at least four patches, each patch including first and second diametrically opposed corners, and third and fourth diametrically opposed corners, and the stripline includes first The strip lines in the first group of strip lines are assigned between the parallel strip lines of the second group and the parallel strip lines of the second group, and the strip lines in the second group of strip lines are Oriented substantially perpendicular to the stripline, wherein the first group of striplines is at least one of the diametrically opposed first and second corners of at least two of the at least four patches. One electrically interconnected together, the second group of striplines being at least 4 Of the third and at least one of the fourth corner opposing at least two each of the diameter direction of the patch, together electrically interconnected, according to claim 1 antenna (400 to 800).   The patch includes at least four patches, each patch including first and second diametrically opposed corners, and third and fourth diametrically opposed corners, and the stripline includes first The strip lines in the first group of strip lines are assigned between the parallel strip lines of the second group and the parallel strip lines of the second group, and the strip lines in the second group of strip lines are Oriented substantially perpendicular to the stripline, wherein the first group of striplines is at least one of the diametrically opposed first and second corners of at least two of the at least four patches. One electrically interconnected together, the second group of striplines being at least 4 At least two of the diametrically opposed third and fourth corners of each of at least two of the patches of the plurality of patches are electrically interconnected together, and the antenna further extends outwardly from each corner of the patch. The antenna (400-600) according to claim 1, comprising one adjusting stub.   The patch includes at least four patches, each patch including first and second diametrically opposed corners, and third and fourth diametrically opposed corners, and the stripline includes first The strip lines in the first group of strip lines are assigned between the parallel strip lines of the second group and the parallel strip lines of the second group, and the strip lines in the second group of strip lines are Oriented substantially perpendicular to the stripline, wherein the first group of striplines is at least one of the diametrically opposed first and second corners of at least two of the at least four patches. One electrically interconnected together, the second group of striplines being at least 4 At least two of the diametrically opposed third and fourth corners of each of at least two of said patches, and electrically interconnecting together, said antenna further from one corner of each of the four patches The antenna (800) of claim 1, comprising a single adjustment stub extending outwardly toward a common point.   The patch includes at least four patches, each patch including first and second diametrically opposed corners, and third and fourth diametrically opposed corners, and the stripline includes first Of the second group of parallel striplines and the third group of striplines, wherein the stripline in the first group of striplines is the second stripline. The striplines in the third group of striplines are oriented substantially perpendicular to the striplines in the group of striplines, and the striplines in the third group of striplines are in the first and second groups of striplines. Oriented substantially at 45 ° to the stripline, the first group of striplines being At least two of each of at least two of the four patches, each of the first and second diametrically opposed corners, are electrically interconnected together, and the second group of striplines includes the at least one At least one of the diametrically opposed third and fourth corners of each of at least two of the four patches are electrically interconnected together, and for at least one group of four patches, the antenna And further comprising an adjustment stub extending outwardly from a corner of each of the four patches comprising the at least one patch group toward a common point, from the strip line of the third group A single stripline connects each adjustment stub with each of the two closest adjustment stubs. The antenna (1000) of claim 1 interconnected.   The patch includes at least four patches, each patch including first and second diametrically opposed corners, and third and fourth diametrically opposed corners, and the stripline includes first Of the second group of parallel striplines and the third group of striplines, wherein the stripline in the first group of striplines is the second stripline. The striplines in the third group of striplines are oriented substantially perpendicular to the striplines in the group of striplines, and the striplines in the third group of striplines are in the first and second groups of striplines. Oriented substantially at 45 ° to the stripline, the first group of striplines being At least two of each of at least two of the four patches, each of the first and second diametrically opposed corners, are electrically interconnected together, and the second group of striplines includes the at least one At least one of the diametrically opposed third and fourth corners of each of at least two of the four patches are electrically interconnected together, and for at least one first group of four patches, The antenna further comprises a short stub extending outwardly from a corner of each of the four patches constituting the at least one patch group toward a common point; One strip line from the third group of strip lines is connected to each short line. Interconnecting each of the two nearest short stubs, and for at least one second group of four patches, the antenna includes a respective one of the four patches comprising the at least one patch group. One adjustment stub extending outwardly from a corner toward a common point, wherein one stripline from the third group of striplines connects each adjustment stub to two closest adjustment stubs; The antenna (1300) of claim 1, interconnected with each other, wherein each adjustment stub extends beyond the interconnection point of the individual stripline and adjustment stub.   The antenna is a linear array antenna defining a first side and a second side, the antenna including at least three patches, each having a first corner near the first side; and Defining a second corner near the second side, and between two adjacent patches, the stripline electrically interconnects the first corner of each patch with the second corner of the adjacent patch. The two striplines intersect and the antenna further comprises at least one adjustment stub extending outwardly from at least one corner of a patch, the corner also connected to the stripline. The antenna (1600) of claim 1.   Electrical to the ground plane and to at least one patch through the at least one transmission line and at least one strip line to feed electromagnetic energy to the antenna and / or extract electromagnetic energy from the antenna The antenna (1900-3300) according to claim 1, further comprising at least one feeding means connected to the antenna.   A first conductive element electrically connected to the ground plane and at least one transmission line and at least one strip for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna; The antenna (1900-3300) according to claim 1, further comprising at least one feeding means having a second conductive element electrically connected to the at least one patch through the line.   In order to feed electromagnetic energy to the antenna and / or extract electromagnetic energy from the antenna, at least one transmission line and at least one strip line on the probe, SMA probe, aperture coupled line, and the ground plane The antenna (1900-3300) according to claim 1, further comprising at least one of microstrip lines that are electrically connected to the at least one patch.   At least two feeding means, each comprising one of a probe, an SMA probe, an aperture coupling line, and a microstrip line, each feeding means feeding electromagnetic energy to the antenna and / or electromagnetic energy; 2. The device of claim 1, diagonally electrically connected to the ground plane and to at least one patch through at least one transmission line and at least one stripline to extract the signal from the antenna. Antenna (2300, 2900, 3200).   Connected to the ground plane and to a plurality of striplines connected to at least one corner of at least one patch to feed electromagnetic energy to the antenna and / or extract electromagnetic energy from the antenna The antenna (1900, 2100, 2500) according to claim 1, further comprising at least one feeding means electrically connected through a transmission line.   Connected to the ground plane and to a plurality of striplines connected to at least one corner of at least one patch to feed electromagnetic energy to the antenna and / or extract electromagnetic energy from the antenna The antenna (1900, 2500) according to claim 1, further comprising at least one feeding means electrically connected through a transmission line, wherein the transmission line is arranged at the center of the second side of the dielectric layer. ).   Connected to the ground plane and to a plurality of striplines connected to at least one corner of at least one patch to feed electromagnetic energy to the antenna and / or extract electromagnetic energy from the antenna 2. The at least one feeding means electrically connected through a transmission line, wherein the transmission line is arranged on the second side of the dielectric layer outside the array of patches. Antenna (2100). A first transmission line connected to the ground plane and to a plurality of substantially parallel first striplines for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna Through which the first transmission line is electrically connected to at least one corner of the at least one patch, wherein the first transmission line is substantially perpendicular to the first strip line, First feeding means positioned outside the array of patches;
A second transmission line connected to the ground plane and to a plurality of substantially parallel second striplines for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna Through which the second transmission line is electrically connected to at least one corner of the at least one patch, wherein the second transmission line is substantially perpendicular to the second stripline, The antenna (2300) of claim 1, further comprising second feed means positioned outside the array of patches, wherein the first stripline is substantially perpendicular to the second stripline. , 2900). A plurality of substantials connected to the ground plane and to at least one first corner of each of the at least one patch for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna. At least one feeding means electrically connected through a transmission line connected to a first parallel strip line, wherein the transmission line is the second of the dielectric layers within the array of patches. At least one power supply means arranged approximately in the center on the side of
A plurality of substantially parallel second striplines connected to at least one second corner of each of the at least one patch, wherein the first stripline is relative to the second stripline; The antenna (2700) of claim 1, further comprising a second stripline that is substantially perpendicular and wherein the first corner is diametrically opposed to the second corner. A first transmission line connected to the ground plane and to a plurality of substantially parallel first striplines for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna Through which the first transmission line is electrically connected to at least one corner of the at least one patch, wherein the first transmission line is substantially perpendicular to the first stripline, First feeding means disposed substantially in the center of the second side of the dielectric layer in an array of patches;
A second transmission line connected to the ground plane and to a plurality of substantially parallel second striplines for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna And second feed means electrically connected to at least one corner of the at least one patch through the second transmission line substantially perpendicular to the second strip line, Disposed substantially in the center of the second side of the dielectric layer in the array of patches, the first stripline being substantially perpendicular to the second stripline, The transmission line further includes a bridge configured substantially at an intersection of the first transmission line and the second transmission line, and the bridge transmits electromagnetic energy to the second transmission line. In order to transmit power over the first transmission line, the first transmission line passes through the opening formed in the dielectric from the second transmission line, the ground plane, and the second dielectric, and The antenna (2900) of claim 1, comprising a via extending to a microstrip disposed on the two dielectrics. A first transmission line connected to the ground plane and to a plurality of substantially parallel first striplines for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna First feeding means electrically connected to at least one corner of at least one patch through the first and second portions of the first transmission line, wherein the first transmission line is relative to the first strip line First feeding means that is substantially right-angled and is located approximately in the center of the second side of the dielectric layer in the array of patches;
A second transmission line connected to the ground plane and to a plurality of substantially parallel second striplines for feeding electromagnetic energy to the antenna and / or extracting electromagnetic energy from the antenna Second feeding means electrically connected to at least one corner of at least one patch through the first and second portions of the second transmission line, wherein the second transmission line is relative to the second stripline Substantially perpendicular and disposed substantially in the center of the second side of the dielectric layer within the array of patches, wherein the first stripline is substantially perpendicular to the second stripline. A second power supply means,
Between the first part and the second part of the first transmission line such that transmission of electromagnetic energy between the first transmission line and the second transmission line is substantially prohibited. A directional coupler configured to provide electrical continuity and to provide electrical continuity between the first and second portions of the second transmission line. The coupler further comprises:
A first microstrip defining a first end connected to the first portion of the first transmission line and a second end connected to the first portion of the second transmission line; A long section (longitudinal section);
A second microstrip defining a first end connected to the second portion of the first transmission line and a second end connected to the second portion of the second transmission line A longitudinal section;
A first microstrip end connection section connected between the first end of the first longitudinal section and the first end of the second longitudinal section;
A second microstrip end connection section connected between the second end of the first longitudinal section and the second end of the second longitudinal section;
An intermediate microstrip connection section connected between an intermediate section of the first longitudinal section and an intermediate section of the second longitudinal section, wherein the first, second and intermediate connection sections are the first Center lines of the first and second longitudinal sections are spaced apart by about 1/4 wavelength, and the center lines of the first connection section and the intermediate connection section are spaced apart by about 1/4 wavelength, and the second line The center line of the connection section and the intermediate connection section is sized so as to be separated by about ¼ wavelength, and the width of the first and second longitudinal sections and the intermediate section is assumed to be an impedance X The antenna (3200) of claim 1, wherein the width of the first and second end connection sections is determined assuming an impedance of about 2X, where X is about 25-100 ohms. . Providing electrical continuity between the first and second portions of the first transmission line and providing electrical continuity between the first and second portions of the second transmission line; A planar microstrip directional coupler configured to substantially inhibit transmission of electromagnetic energy between the first transmission line and the second transmission line,
A first microstrip length defining a first end connected to the first portion of the first transmission line and a second end connected to the first portion of the second transmission line; Interval,
A second microstrip length defining a first end connected to the second portion of the first transmission line and a second end connected to the second portion of the second transmission line; Interval,
A first microstrip end connection section connected between the first end of the first longitudinal section and the first end of the second longitudinal section;
A second microstrip end connection section connected between the second end of the first longitudinal section and the second end of the second longitudinal section;
An intermediate microstrip connection section connected between an intermediate point of the first longitudinal section and an intermediate point of the second longitudinal section, wherein the first, second and intermediate connection sections comprise the first Center lines of the first and second longitudinal sections are spaced apart by about 1/4 wavelength, and the center lines of the first connection section and the intermediate connection section are spaced apart by about 1/4 wavelength, and the second line The center line between the connection section and the intermediate connection section is sized so as to be spaced apart by about ¼ wavelength, and the widths of the first and second longitudinal sections and the intermediate section are defined as impedance X A coupler that is determined assuming that the width of the first and second end connection sections is determined assuming an impedance of about 2X, where X is about 25-100 ohms.   28. The coupler of claim 27, wherein the first and second ends of the first and second longitudinal sections are each chamfered at an angle of about 45 degrees. A microstrip array antenna,
A single layer of dielectric material;
A ground plane adjacent to the first side of the dielectric material;
A plurality of patches adjacent to a second side of the dielectric material opposite the first side;
A power supply terminal;
A plurality of stripline conductors that physically connect the feeding terminal to each of the plurality of patches, a cavity is formed between the patches, and the stripline and the ground plane are fixed in the cavity. An antenna configured such that waves are formed, whereby there are several nodes of standing waves on each of the stripline conductors. A method for designing a microstrip array antenna comprising:
Attaching a ground plane to the first side of the planar dielectric;
Configuring a radiating patch, a feed terminal, and an associated conductive material connecting the feed terminal to each of the radiating patch on a second side of the planar dielectric opposite the first side; Including, forming a standing wave having a plurality of nodes in a cavity between the patch and the associated conductive material and the ground plane, wherein at least some nodes of the standing wave are associated with the associated conductive A method that is consistent with the position of the material.   32. The method of claim 30, wherein the associated conductive material is configured as a stripline. A method for designing a microstrip array antenna comprising:
Attaching a ground plane to the first side of the planar dielectric;
Configuring a radiating patch, a feed terminal, and an associated conductive material connecting the feed terminal to each of the radiating patch on a second side of the planar dielectric opposite the first side; A method comprising: forming a standing wave having a plurality of nodes in a cavity between the patch and the associated conductive material and the ground plane to provide a predetermined distribution of electromagnetic force on the radiating patch.   35. The method of claim 32, wherein the associated conductive material is configured as a stripline and the predetermined distribution is substantially uniform.   33. The method of claim 32, wherein the associated conductive material is configured as a stripline, and the predetermined distribution is tapered to minimize sidelobe energy distribution. A planar microstrip array antenna,
A single layer of dielectric material;
A ground plane adjacent to the first side of the dielectric material;
A plurality of patches opposite to the first side and adjacent to the second side of the dielectric material, wherein all of the patches used in an operating mode are of the same physical size;
A power supply terminal;
An antenna comprising a plurality of stripline conductors interconnecting the feed terminals directly to each of the plurality of patches; A method for distributing EM (electromagnetic) energy between first and second energy sources and their individual energy sinks, wherein the first and second energy sources are in the same plane. Are physically connected to their individual energy sinks via first and second sets of crossed conductors having different angular orientations,
Providing a resonant cavity adjacent to a plane of the intersecting conductor;
Generating first and second standing waves of the first and second angular orientations from the first and second EM sources, whereby the first and second standing waves of A method in which nodes occur at at least some of the intersections of the first and second sets of crossing conductors, so that bimodal excitations are independent of each other.   40. The method of claim 36, wherein the crossing conductor is a stripline. An antenna,
A ground plane;
A surface area comprising a radiating array element, a signal source terminal, and an associated conductive material interconnecting the radiating patch and the signal source terminal;
The surface area configured to generate a standing wave having nodes present in both the radiating array element and the associated conductive material upon application of an EM (electromagnetic) force to the antenna and the ground plane. And an antenna comprising a resonant signal cavity in between.   40. The apparatus of claim 38, wherein the radiating array element is a patch of conductive material and the associated conductive material comprises a stripline element. A microstrip planar array antenna,
A plurality of radiating array elements in a planar array;
A power supply terminal in the planar array;
A plurality of associated conductive material elements in the planar array, whereby the feed terminal is physically connected to each of the plurality of substantially equal sized patches;
An antenna comprising a resonant cavity adjacent to the planar array configured such that a standing wave formed therein has a node at the intersection of two vertical and horizontal striplines. The radiating array elements are radiating patches and are substantially the same size for maximum directivity;
41. The apparatus of claim 40, wherein the associated conductive material element is a stripline. A microstrip single plane array antenna that can be used without modification for circular and linearly polarized beam signals,
A plurality of radiating patches in a planar array;
First and second feed terminals in the planar array;
The first and second sets of stripline conductors in the planar array, wherein the feed terminals are each oriented in different angular directions so as to form a plurality of cross-shaped intersections. And a second set of stripline conductors, wherein the first and second sets of stripline conductors are physically connected to each of the plurality of substantially equal sized patches;
An antenna comprising a standing cavity formed within itself and a resonant cavity adjacent to the planar array configured to have nodes that coincide with a cross-shaped intersection of the stripline and a majority of the radiating patch.   43. The apparatus of claim 42, wherein the radiating patches are substantially the same size for maximum directivity.   44. The antenna of claim 41 or 43, wherein the patch is square. A method of increasing the transmission efficiency of a microstrip array antenna comprising a radiating patch and a source terminal in a given plane juxtaposed with a resonant cavity, comprising:
Electrically connecting a source terminal to each of the radiating patches with a plurality of conductive strips;
Configuring antenna elements such that standing waves generated in the resonant cavity have nodes at most intersection points of the conductive strip in a mode excitation manner, thereby minimizing the level of crosstalk. Method. An antenna (100-3300),
A dielectric layer defining a first side and a second side;
A conductive ground plane disposed on the first side of the dielectric layer;
An array of radiating patches disposed and spaced apart on the second side of the dielectric layer;
An antenna comprising at least one interconnect element disposed on the second side of the dielectric layer and electrically interconnected with at least one corner of each patch of the array of patches.   47. The antenna of claim 46, wherein the at least one interconnect element and the patch define one surface of a leakage cavity that effectively includes standing waves.   47. The antenna of claim 46, wherein the at least one interconnect element is operative to guide a standing wave power flow formed in a cavity delimited by the dielectric layer.   47. The antenna of claim 46, wherein the at least one interconnect element operates in conjunction with the patch to define an antenna bandwidth.   47. The antenna of claim 46, wherein the at least one interconnect element operates in the context of the patch and defines a standing wave resonant frequency of a cavity formed in the boundary of the dielectric layer.

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