KR101572873B1 - Dual directional inverter of electric energy storage system - Google Patents

Dual directional inverter of electric energy storage system Download PDF

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Publication number
KR101572873B1
KR101572873B1 KR1020150053432A KR20150053432A KR101572873B1 KR 101572873 B1 KR101572873 B1 KR 101572873B1 KR 1020150053432 A KR1020150053432 A KR 1020150053432A KR 20150053432 A KR20150053432 A KR 20150053432A KR 101572873 B1 KR101572873 B1 KR 101572873B1
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South Korea
Prior art keywords
voltage
output
current
unit
converter
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KR1020150053432A
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Korean (ko)
Inventor
한병철
김민성
이성호
손성호
김수아
이진수
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포항공과대학교 산학협력단
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/36—Arrangements for transfer of electric power between ac networks via a high-tension dc link
    • H02J3/383—
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • H02J3/40—Synchronising a generator for connection to a network or to another generator
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M2001/0009—
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E60/00—Enabling technologies; Technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02E60/60—Arrangements for transfer of electric power between AC networks or generators via a high voltage DC link [HVCD]

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The present invention relates to a technique for outputting power having a high power density and realizing a low cost in realizing a bidirectional inverter for bidirectionally converting power in cooperation with a system power supply in a system for storing electrical energy.
In accordance with the present invention, a DC voltage stored in an electric energy storage system is converted into a voltage in the form of full-wave rectification, or vice versa, using a cook converter of a type including a boost converter type and a buck converter type, And the voltage of the sinusoidal wave full wave rectified is converted into the voltage of the sinusoidal wave or the voltage of the sinusoidal wave is rectified by full wave through the folding bridge circuit part.

Description

BACKGROUND OF THE INVENTION 1. Field of the Invention [0001] The present invention relates to a dual-

In particular, the present invention relates to a technique for bi-directionally converting power in cooperation with a system power supply in a system for storing electrical energy. More particularly, the present invention relates to a technique of converting a DC power stored in a battery into a power source of an AC system or vice versa, And more particularly to a bi-directional inverter of an electric energy storage system.

Generally, a bidirectional inverter applied to an electric energy storage system or the like refers to a device that converts a direct current (DC) power source to an alternating current (AC) system power source or vice versa and converts an AC system power source to a DC power source. There are various devices for supplying power to the electric energy storage system, for example, a power supply of an electric energy storage system may be included. The electrical energy storage system may include a battery.

There are various requirements for implementing such a bidirectional inverter. Among them, it is desperately required to realize low cost and convert it to a power source having high power density and output it.

Nevertheless, a bidirectional inverter applied to a conventional electric energy storage system or the like is difficult to implement at a low cost and has a defect that it can not be converted into a power source having a high power density.

A problem to be solved by the present invention is to provide a DC converter using a Cuk converter of a type including a boost converter type and a buck converter type, Voltage or vice versa, and the sine-wave voltage through the unfolding bridging circuitry converts the full-wave rectified voltage to a sinusoidal voltage or vice versa.

According to an aspect of the present invention, there is provided a bi-directional inverter of an electric energy storage system including a cook converter including a boost converter unit and a buck converter unit, wherein the DC voltage supplied from the power source is a sinusoidal voltage A DC-DC converter unit for converting the DC voltage into a full-wave rectified voltage and outputting the DC voltage, and vice versa; An unfolding bridge circuit unit converting the sinusoidal voltage output from the dishi-DC converter unit to a negative polarity and generating an output voltage of a sinusoidal wave; And a main controller for controlling operation of the dictation-to-dictation converter based on an input / output voltage and an input / output current of the dictation-to-dictation converter and an output voltage of the unfolding bridge circuit.

The present invention uses a cook converter of a type including a boost converter type and a buck converter type to convert a DC voltage stored in an electric energy storage system into a voltage of a sine wave voltage that is full wave rectified or vice versa, The voltage of the full-wave rectified voltage is converted into the voltage of the sinusoidal wave or vice versa, and the converted voltage is connected to the system power supply. Thus, the bidirectional inverter can be implemented at a low cost, and a power having high power density can be output There is an effect.

1 is a block diagram of a bi-directional inverter of an electric energy storage system according to an embodiment of the present invention.
FIG. 2 (a) and FIG. 2 (b) are output waveform diagrams of the dish-saw converter section and the unfolding bridge circuit section in FIG.
FIG. 3A is a detailed circuit diagram of the dish-saw converter in FIG.
3B is a detailed circuit diagram of the unfolding bridge circuit portion in FIG.
4A and 4B are circuit diagrams illustrating an operation of the dash-and-dia converter according to the first switch on / off.
5A and 5B are circuit diagrams illustrating an operation of the dash-and-dict converter unit according to the second switch on / off.
6A is a detailed block diagram of a main control unit for switching control of a boost converter when converting a decibel voltage into a voltage of a sinusoidal wave type full wave rectified.
6B is a detailed block diagram of a main control unit for switching control of a buck converter when a sinusoidal-type full-wave rectified voltage is converted into a dicing voltage.

Hereinafter, preferred embodiments of the present invention will be described in detail with reference to the accompanying drawings.

1 is a block diagram of a bidirectional inverter of an electric energy storage system having a high power density according to an embodiment of the present invention. As shown in FIG. 1, a DC power source 110, a DC-DC converter unit 120, An unfolding bridge circuit unit 130, a system power supply 140, a first voltage / current sensor unit 151, a second voltage / current sensor unit 152, an output voltage sensor unit 153, And a control unit 160.

The power supply 110 is supplied with the power of the power stored in the electric energy storage system. The voltage of the power supply varies according to the amount of solar radiation or ambient temperature.

The DC-DC converter unit 120 includes a Cuk converter having a boost converter unit and a buck converter unit. The DC-DC converter unit 120 supplies the DC voltage supplied from the DC power source 110 to the DC- A sinusoidal voltage is converted into a full-wave rectified voltage and output, or vice versa.

The dicing-to-dither converter unit 120 may output a sine wave voltage with a full-wave rectified voltage by setting different duty ratios for each sampling period. The dictation-to-dictation converter unit 120 can perform both the operation of raising and lowering the voltage internally by using the above-described cook converter instead of using only the buck converter or the boost converter. Accordingly, the dic-decy converter unit 120 can output power having a high power density and can minimize ripple in both input and output power. In addition, since the area of the voltage conversion ratio is widened, it can be connected to various voltage region dicinks, thereby improving compatibility. By connecting the boost converter unit and the buck converter through the transformer, the dicing-to-dike converter unit 120 can obtain an insulation effect between the input and output power, reduce the duty ratio input area of the cook converter, It is possible to avoid a high duty ratio area where the voltage change due to the duty ratio change is sensitive.

3A is a circuit diagram showing an embodiment of the dictation-to-dither converter unit 120. As shown in FIG. 3A, the boost converter unit 121 and the buck converter unit 123 are connected to the boost converter unit 121, The buck converter unit 123 has a structure that is insulated by the transformer 122.

Boost converter 121 is either side terminal of the input voltage (Vin), an inductor (L1) connected in series between the both side terminals of the capacitor (C1) and the transformer primary winding of the (122) (N P), an input voltage (Vin) And a switch S1 connected between the connection node between the inductor L1 and the capacitor C1 and the other terminal of the input voltage Vin. Here, the switch S1 may be implemented as a MOS transistor. In the following description, the switch S1 is referred to as a MOS transistor.

The buck converter 123 is connected in series between the both side terminals of the output voltage (V o1), the inductor (L2), a capacitor (C4) and a secondary winding (N S) and the inductor (L2) of the transformer (122) And a switch S2 connected between a connection node of the capacitor C4 and the other terminal of the output voltage V o1 . Here, the switch S2 may be implemented as a MOS transistor, and the switch S1 is hereinafter referred to as a MOS transistor.

4A is a schematic diagram of the current flow when the MOS transistor S2 is turned off in the dash-and-dia converter unit 120 and the MOS transistor S1 is turned on. S2 is off and the MOSFET transistor S1 is turned off, the dc-to-dc converter section 120 refers to the dc-to-dc converter section 120 to refer to the flow of current when the sinusoidal voltage is full-wave rectified The operation of converting to a voltage will be described as follows.

4A, when the MOS transistor S1 is turned on by the pulse width modulation signal PWM1 supplied from the main control unit 160 in the dash-and-dia converter unit 120, only the inductor L1 is supplied with the input voltage Vin Is supplied to increase the current flowing through the inductor L1, whereby electric energy is accumulated in the inductor L1. This operation is similar to that of the conventional switch-on mode of the boost converter. The electric energy charged in the capacitor C1 is transmitted to the primary coil N P of the transformer 122 and the electric energy corresponding thereto is transmitted to the secondary coil N S of the transformer 122. Electrical energy that has been charged into the electric energy and the capacitor (C3) transmitted to the secondary windings (N S) of the transformer (122) is released with is transmitted to the inductor (L2) and a capacitor (C4). Therefore, the output voltage (V O1 ) of the DC-DC converter unit 120 is the same as the voltage across both terminals of the capacitor C4. This operation is similar to the operation of the conventional buck converter in the switch-off mode.

Referring to FIG. 4B, when the MOS transistor S1 is turned off by the pulse width modulation signal PWM1 in the dash-and-dia converter 120, the electric energy stored in the inductor L1 is discharged. At this time, The voltage (Vin) and the voltage polarity of the inductor (L1) are equal to each other. Thus, the summed voltage of the input voltage (Vin) and an inductor (L1) is transmitted to the capacitor (C1) and the primary winding (N P) of the transformer (122). Therefore, the voltage boosted by the turns ratio N P / N S of the primary coil N P and the secondary coil N S of the transformer 122 is transmitted from the transformer 122 to the capacitor C 3, do. This operation is similar to the operation in the switch-off mode of the conventional boost converter. Since the electric energy accumulated in the inductor L2 is discharged and charged to the capacitor C4, the amount of the output current of the DSSC 120 is reduced. This operation is similar to the operation of the switch-on mode of the buck converter.

The conventional D / A converter unit outputs the decibel voltage, whereas the D / D converter unit 120 outputs the voltage in the form of full wave rectification of the sinusoidal voltage, so that the capacitor C4 having a small capacity can be used.

5A is a schematic diagram illustrating a current flow when the MOS transistor S1 is turned off and the MOS transistor S2 is turned on in the decode-and-decyption converter unit 120, and FIG. 5B is a diagram illustrating a MOS transistor S1 ) Is off and the current flows when the MOS transistor (S2) is turned off. Referring to these figures, the voltage of the form in which the sinusoidal voltage is full-wave rectified in the dishi-converter unit (120) The following description will be given.

5A, when the MOS transistor S2 is turned on by the pulse width modulation signal PWM2 supplied from the main control unit 160 in the dash-and-dia converter unit 120, a voltage is supplied only to the inductor L2 The current flowing through the inductor L2 is increased, whereby electric energy is accumulated in the inductor L2. This operation is similar to that of the conventional switch-on mode of the boost converter. And, it is transmitted to the capacitor (C3) (N P) 1 the secondary coil of the electrical energy that has been charged is transferred to secondary windings (N S) of the transformer (122) of electric energy in accordance with it is the transformer 122 to the. The electric energy transferred to the primary coil N P of the transformer 122 and the electric energy charged in the capacitor C1 are discharged together and transferred to the inductor L1 and the capacitor C2. Therefore, the output voltage of the Dish-Dish convertor unit 120 is equal to the voltage across the two terminals of the capacitor C2. This operation is similar to the operation of the conventional buck converter in the switch-off mode.

Referring to FIG. 5B, when the MOS transistor S2 is turned off by the pulse width modulation signal PWM2, the electric energy stored in the inductor L2 is discharged. At this time, The voltage and the voltage polarity of the inductor L2 are equal to each other. Thus, the summed voltage of the input voltage and the inductor (L2) is transmitted to the capacitor (C3) and a secondary winding (S N) of the transformer (122). Therefore, the voltage lowered by the turns ratio N S / N P of the secondary coil N S and the primary coil N P of the transformer 122 is transmitted from the transformer 122 to the capacitor C 1, do. This operation is similar to the operation in the switch-off mode of the conventional boost converter. Since the electric energy stored in the inductor L1 is discharged and charged in the capacitor C2, the amount of the output current of the DSSC 120 is reduced. This operation is similar to the operation of the switch-on mode of the buck converter.

The unfolding bridge circuit unit 130 outputs an even-numbered section (or an odd-numbered section) of a voltage of a full-wave rectified voltage of the sinusoidal voltage output from the dish- And generates the output voltage V o2 of the sinusoidal waveform as shown in FIG. 2 (b), and then connects the output voltage V o2 to the system power supply 140. On the other hand, the unfolding bridge circuit unit 130 converts the voltage of the sinusoidal waveform as shown in FIG. 2 (b) into the voltage of the sinusoidal voltage as shown in FIG. 2 (a).

3B is a circuit diagram showing an embodiment of the unfolding bridge circuit unit 130. As shown in FIG. 3B, the unshielded bridge circuit unit 130 is connected in series between two input terminals connected to the output voltage V O1 of the dish- Switches S5 and S6 connected in series between the two input terminals connected to the output voltage V O1 of the dish-to-be-decode unit 120 and switches S5 and S6 of the switches S5 and S6, and the output voltage inductor (L3) connected between one terminal of the (V O2) and a connection node and an output voltage capacitor (C5) connected between the other terminal of the (V O2) of the switch (S5, S6). Here, the switches S3-S6 may be implemented as MOS transistors, and the switch S1 will be referred to as a MOS transistor in the following description.

3B, when the system power supply 140 is positive (+), the first switching mode is set so that the MOS transistors S4 and S5 are turned on and the MOS transistors S3 and S6 are turned off, Th sinusoidal voltage is output as it is as the output voltage V O2 . When the system power supply 140 is negative (-), the second switching mode is set so that the MOS transistors S4 and S5 are turned off and the MOS transistors S3 and S6 are turned on, The even-numbered section is switched to the negative polarity. Thus, the output voltage V o2 of the unfolding bridge circuit unit 130 is output as a voltage of a sinusoidal waveform like that of FIG. 2 (b). For example, when the frequency of the system power supply 140 is 60 Hz, the pulse width modulation signals PWM3, PWM4, PWM5, and PWM6 supplied at the corresponding periods are supplied to the MOS transistors S3, S4, S4, S6) are switched to the first switching mode and the second switching mode.

An LC filter composed of an inductor L3 and a capacitor C5 connected to the output terminal of the unfolding bridge circuit part 130 serves to minimize power ripple. The unshielded bridge circuit unit 130 is connected to the dash-and-dia converter unit 120 in the form of a full-wave rectified sine wave voltage, Only the polarity of the voltage is changed. Therefore, since the role of the LC filter formed of the inductor L3 and the capacitor C5 can be minimized, the capacitances of the inductor L3 and the capacitor C7 can be minimized.

The first voltage / current sensor unit 151 detects a voltage and a current input from the decision power source 110 and outputs an input voltage V in and an input current i in according to the detected voltage and current.

The second voltage / current sensor unit 152 detects the full-wave rectified voltage and current output from the dish-to-decode converter unit 120 and outputs an output voltage V o1 and an output current i o1 corresponding thereto .

The output voltage sensor unit 153 detects a voltage output from the unfolding bridge circuit unit 130 and outputs an output voltage V o2 corresponding thereto.

The main controller 160 controls the input voltage V in and the input current i in that are output from the first voltage / current sensor 151 and the output Generates a pulse width modulation signal PWM1 having a duty ratio based on a voltage V o1 and an output current i o1 and an output voltage V o2 output from the output voltage sensor unit 153, The converter unit 121 controls the switching operation of the MOS transistor S1 or generates the pulse width modulation signal PWM2 to control the switching operation of the MOS transistor S2 in the buck converter unit 123. [ Accordingly, the DC-DC converter 120 converts the DC input voltage V in into the output voltage V o1 of the sine wave and outputs the converted output voltage V o1 . Referring to FIGS. 6A and 6B, The following is a more detailed description.

6A is a detailed block diagram showing a first embodiment for generating a pulse width modulation signal PWM1 when the main control unit 160 converts a dicing voltage into a sinusoidal wave full wave rectified voltage, Similarly, the first reference duty voltage generator 161A, the phase lock loop unit 162, the first reference output current calculator 163A, the first summer 164A, the first controller 165A, A first comparator 166A, a first comparator 167A, and a first gate driver 168A.

The first reference duty voltage generating unit 161A generates the first reference duty voltage Vout using the input voltage V in supplied from the first voltage / current sensor unit 151 and the output voltage V o1 supplied from the second voltage / , And outputs the reference duty voltage (V duty_ref ) using the following Equation (1). The reference duty voltage V duty_ref is a voltage used by the dictation-to-dither converter unit 120 to convert the input voltage V in into a voltage V o1 in which a sinusoidal voltage is full-wave rectified.

Figure 112015036870510-pat00001

Here, V o1 _ref denotes a reference voltage of a voltage in which the sinusoidal voltage to be converted from the input voltage V in is fully rectified, and N S / N P denotes a transformer 122).

However, when the load is an unstable system voltage, the DC-DC converter unit 120 has difficulty in generating a normal alternating current using only the reference duty voltage V duty_ref . This view is further to seek additional duty voltage (V duty _add) through the following steps.

The phase lock loop unit 162 derives a final phase value that is synchronized with the output voltage V o2 supplied from the output voltage sensor unit 153.

In order to generate a power source having the same phase as the output power source, that is, the system power source 140, the first reference output current calculator 163A calculates a first reference output current value 163A based on the sine wave current value (a i) and to apply the frequency (Wd) synchronized to the 60Hz determined on the basis of the last phase value in the following <equation 2> is obtained for any DC current that is, based on the input current (i in _ref).

Figure 112015036870510-pat00002

The first summing amplifier 164A receives the reference input current i in_ref supplied from the first reference output current calculator 163A and the reference output current i o1_ref supplied from the second voltage / ) And outputs a difference current (i diff ) corresponding thereto.

A first controller (165A) is the first summer differential current outputted from (164A) (i diff) a proportional-integral output (Proportional-Integral) by adding the duty voltage (V duty _add) thereof.

The second summer 166A sums the reference duty voltage (V duty_ref ) and the additional duty voltage (V duty_add ) and outputs a duty voltage (V duty ) corresponding thereto.

The first comparator 167A compares the duty voltage (V duty ) input from the second summer 166A to the non-inverting input terminal with the triangular waveform RW input to the inverting input terminal, And outputs a pulse width modulation signal.

The first gate driver 168A appropriately processes the pulse width modulation signal output from the first comparator 167A and outputs a first pulse width modulation signal PWM1 corresponding thereto. The pulse width modulation signal PWM1 is supplied to the gate of the MOS transistor S1 of the boost converter unit 121 to control the switching operation of the MOS transistor S1.

Thus, when the MOS transistor S1 is switched by the pulse width modulation signal PWM1, the MOS transistor S2 is maintained in the OFF state by the pulse width modulation signal PWM2.

As described above, the first comparator 167A simply compares the reference duty voltage V duty_ref supplied from the first reference duty voltage generator 161A with the triangular waveform RW, Outputting a pulse width modulated signal having a duty ratio in comparison with the duty voltage (V duty ) and the triangular waveform (RW) obtained through the above-described process, instead of outputting the modulated signal, It is possible to output a normal alternating current through the converter unit 120 and the unfolding bridge circuit unit 130.

6B is a detailed block diagram showing a second embodiment for generating the pulse width modulation signal PWM2 in the main controller 160. As shown in FIG. 6B, the second reference duty voltage generator 161B, A third summing amplifier 164B, a second controller 165B, a fourth summing amplifier 166B, a second comparator 167B and a second gate driver 168B.

The second reference duty voltage generator 161B generates and outputs the reference duty voltage V duty_ref on the same principle as the first reference duty vector generator 161A.

The second reference output current calculating section (163B) is obtained based on the input current (i in _ref) based on the input current (i in) supplied from the first voltage / current sensor 151.

A third summer (164B) is the reference input current (i in _ref) and a first voltage / current sensor 151 obtain the differential value of the reference output current (i O1 _ref) supplied primary current (i diff hence from ).

A second controller (165B) is proportional to the primary current (i diff) output from said third summer (164B) - and outputs the added duty voltage (V duty _add) accordingly by integration.

The fourth summer 166B sums the reference duty voltage (V duty_ref ) and the additional duty voltage (V duty_add ) and outputs a duty voltage (V duty ) corresponding thereto.

The second comparator 167B compares the duty voltage (V duty ) input from the fourth summer 166B to the non-inverting input terminal with the triangular waveform RW input to the inverting input terminal and has a duty ratio corresponding thereto And outputs a pulse width modulation signal.

The second gate driver 168B appropriately processes the pulse width modulated signal output from the second comparator 167B and outputs the second pulse width modulated signal PWM2 accordingly. The pulse width modulation signal PWM2 is supplied to the gate of the MOS transistor S2 of the buck converter unit 123 to control the switching operation of the MOS transistor S2.

As described above, when the MOS transistor S2 is switched by the pulse width modulation signal PWM2, the MOS transistor S1 maintains the OFF state by the pulse width modulation signal PWM1.

Although the preferred embodiments of the present invention have been described in detail above, it should be understood that the scope of the present invention is not limited thereto. These embodiments are also within the scope of the present invention.

110: power supply of the DC power supply 120: DC-DC converter unit
121: boost converter section 122: transformer
123: Buck converter section 130: Unfolding bridge circuit section
140: system power supply 151: first voltage / current sensor unit
152: second voltage / current sensor unit 153: output voltage sensor unit
160: main control unit 161A: first reference duty voltage generating unit
162: phase lock loop unit 163A: first reference output current calculation unit
163B: a second reference output current calculation section 164A: a first sum-
164B: third adder 165A: first controller
165B: second controller 166A: second summer
166B: fourth adder 167A: first comparator
167B: second comparator

Claims (20)

The present invention provides a cook converter including a boost converter unit and a buck converter unit. The DC / DC converter unit converts a DC voltage supplied from the power source to a voltage of a full-wave rectified voltage and outputs a voltage of a full- A DC-DC converter for converting the DC voltage into a DC voltage;
And an unfolding bridge circuit part for converting the sinusoidal voltage outputted from the dishi-DC converter part into a full-wave rectified voltage to generate a sinusoidal output voltage by converting an even- ; And
And a main controller for controlling operation of the dictation-to-dictation converter based on an input / output voltage and an input / output current of the dictation-to-dictation converter and an output voltage of the unfolding bridge circuit,
The main control unit
A first voltage / current sensor unit for sensing an input voltage and an input current of the dish-toe converter unit;
A second voltage / current sensor unit sensing a first voltage and a first current output from the dicode-to-digital converter unit; And
And an output voltage sensor unit for sensing a second voltage output from the unfolding bridge circuit unit.
2. The apparatus of claim 1, wherein the dish-
Wherein a duty ratio is set differently for each sampling period, and a full-wave rectified waveform voltage corresponding thereto is output.
2. The apparatus of claim 1, wherein the dish-
A boost converter unit that operates in a switch-on mode in which a first switch inside is boosted and boosts a DC voltage supplied from the decision power supply and periodically accumulates or operates in a switch-off mode in which the first switch is off;
A buck converter unit that operates in a switch-on mode in which a second switch inside is turned on to drop a voltage accumulated in the boost converter unit and outputs the voltage, or operates in a switch-off mode in which the second switch is off; And
And a transformer for connecting an output terminal of the boost converter section and an input terminal of the buck converter section in an insulated state.
4. The power converter according to claim 3, wherein the boost converter
A first inductor and a first capacitor connected in series between one terminal of the input voltage and one of the taps of the primary coil of the transformer;
A first switch connected between a common node between the first inductor and the first capacitor and the other terminal of the input voltage; And
And a second capacitor connected between both terminals of the input voltage. &Lt; RTI ID = 0.0 &gt; 11. &lt; / RTI &gt;
5. The bi-directional inverter of an electric energy storage system according to claim 4, wherein the first switch is a MOS transistor.
6. The bi-directional inverter of an electric energy storage system according to claim 5, wherein a first diode is connected between both terminals of the MOS transistor.
4. The buck converter of claim 3,
A third capacitor and a second inductor connected in series between one of the taps of the secondary coil of the transformer and one terminal of the first output voltage;
A second switch connected between a connection node between the third capacitor and the second inductor and the other terminal of the first output voltage; And
And a fourth capacitor connected between both terminals of the first output voltage.
8. The bi-directional inverter of an electric energy storage system according to claim 7, wherein the second switch is a MOS transistor.
The apparatus of claim 1, wherein the unfolding bridge circuitry
A third MOS transistor and a fourth MOS transistor connected in series between both input terminals connected to a first output voltage of the dicode-to-DC converter unit; And
And a fifth MOS transistor and a sixth MOS transistor connected in series to both input terminals connected to the first output voltage of the DC-DC converter unit.
10. The apparatus of claim 9, wherein the unfolding bridge circuitry
The fourth MOS transistor and the fifth MOS transistor are turned on in the positive period of the sinusoidal wave and the third MOS transistor and the sixth MOS transistor are turned off to output the voltage in the form of full wave rectification of the sine wave voltage ,
In the negative polarity period, the fourth MOS transistor and the fifth MOS transistor are turned off, and the third MOS transistor and the sixth MOS transistor are turned on to turn the even-numbered period among the voltages of the full- And outputs the converted electric energy to the electric energy storage system.
11. The bi-directional inverter of an electric energy storage system according to claim 10, wherein the cycle of the sinusoidal wave is 60 Hz.
10. The bi-directional inverter of an electric energy storage system according to claim 9, wherein the unfolding bridge circuit part includes an LC filter at an output end.
13. The apparatus of claim 12, wherein the LC filter
A fifth capacitor connected between the connection node of the fifth MOS transistor and the sixth MOS transistor and the other terminal of the second output voltage; And
And a third inductor connected between the connection node of the fifth MOS transistor and the sixth MOS transistor and one terminal of the second output voltage to remove the ripple of the output voltage of the sinusoidal wave. Bidirectional inverter of storage system.
delete 2. The apparatus of claim 1, wherein the main control unit
An input voltage and an input current output from the first voltage / current sensor unit;
An output voltage and an output current output from the second voltage / current sensor unit; And
And a second pulse width modulation signal having a duty ratio based on an output voltage output from the output voltage sensor unit to control the switching operation of the boost converter provided in the dish- Bidirectional inverter of storage system.
2. The apparatus of claim 1, wherein the main control unit
An input voltage and an input current output from the first voltage / current sensor unit;
An output voltage and an output current output from the second voltage / current sensor unit; And
And a second pulse width modulation signal having a duty ratio based on an output voltage output from the output voltage sensor unit to control the switching operation of the boost converter provided in the dish- Bidirectional inverter of storage system.
2. The apparatus of claim 1, wherein the main control unit
A first reference duty voltage generator for obtaining a reference duty voltage based on the input voltage and the first output voltage of the DC-DC converter;
A phase locked loop unit for deriving a final phase value to be synchronized with a second output voltage outputted from the unfolding bridge circuit unit;
A frequency synchronized to 60 Hz is obtained on the basis of the current value of the sinusoidal wave obtained from the current value of the power supplied from the outside and the final phase value in accordance with the randomly designed amount of power so as to generate the power having the same phase as the system power, A first reference output current calculator for calculating and outputting a reference input current based on the value and the frequency;
A first summing unit for obtaining a difference between the reference output current and a first output current outputted from the dish-to-decode unit and outputting a difference current according to the difference;
A first controller proportional-integrating the differential current to output a corresponding additional duty voltage;
A second summing unit for summing the reference duty voltage and the additional duty voltage and outputting a duty voltage according to the sum;
A first comparator for comparing the duty voltage with a triangular waveform to produce a first pulse width modulated signal having a duty ratio accordingly; And
And a first gate driver for generating a first pulse width modulation signal based on a pulse width modulation signal output from the first comparator and controlling a switching operation of the boost converter, .
The bi-directional inverter of an electric energy storage system according to claim 17, wherein the first reference duty voltage generator obtains the reference duty voltage (V duty_ref ) using the following equation.
Figure 112015094303661-pat00003

Here, V o1_ref is the dish-a DC converters add the reference voltage of the voltage of the full wave rectified form of a sinusoidal voltage to be converted from the input voltage, V in is the DC-the input voltage DC converter portion, N S / N P is And the winding ratio of the transformer provided in the dishi-decoder converter unit.
19. The bi-directional inverter of an electric energy storage system according to claim 18, wherein the first reference output current calculator obtains the reference input current (i in_ref ) using the following equation.

Figure 112015055220712-pat00004

Here, A i is a current value of the sinusoidal wave, and ω d is a frequency synchronized with the system power supplied from the phase lock loop unit.
2. The apparatus of claim 1, wherein the main control unit
A second reference duty voltage generator for obtaining a reference duty voltage based on the input voltage and the first output voltage of the DC-DC converter;
A second reference output current arithmetic unit for obtaining and outputting a reference input current based on the input current of the diche-
A third summing unit for obtaining a difference between the reference input current and the reference output current outputted from the dishi-dy converter unit and outputting a difference current according to the difference;
A second controller proportional-integrating the differential current to output a corresponding additional duty voltage;
A fourth summing unit for summing the reference duty voltage and the additional duty voltage and outputting a duty voltage according to the sum; And
A second comparator for comparing the duty voltage with a triangular waveform to produce a second pulse width modulated signal having a duty ratio therefrom; And
And a second gate driver for generating a second pulse width modulated signal based on the pulse width modulated signal output from the second comparator and controlling the switching operation of the buck converter. Bidirectional inverter.
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Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR20170142362A (en) 2016-06-17 2017-12-28 현대일렉트릭앤에너지시스템(주) Relay driver and inverter system having thereof
KR101836587B1 (en) * 2015-12-15 2018-03-09 현대오트론 주식회사 Method of injecting current for full cell stack and apparatus performing the same
KR101920469B1 (en) * 2017-04-03 2018-11-20 포항공과대학교 산학협력단 Grid connected single-stage inverter based on cuk converter
KR20220106511A (en) 2021-01-22 2022-07-29 전북대학교산학협력단 Bidirectional Isolated Inverter circuit and Energy Storage System using the same
KR20230019566A (en) * 2021-08-02 2023-02-09 한국에너지기술연구원 Power conversion system for salinity gradient power generation

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2009539337A (en) * 2006-06-02 2009-11-12 シーメンス アクチエンゲゼルシャフト エスターライヒ Inverter circuit

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2009539337A (en) * 2006-06-02 2009-11-12 シーメンス アクチエンゲゼルシャフト エスターライヒ Inverter circuit

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR101836587B1 (en) * 2015-12-15 2018-03-09 현대오트론 주식회사 Method of injecting current for full cell stack and apparatus performing the same
KR20170142362A (en) 2016-06-17 2017-12-28 현대일렉트릭앤에너지시스템(주) Relay driver and inverter system having thereof
KR101920469B1 (en) * 2017-04-03 2018-11-20 포항공과대학교 산학협력단 Grid connected single-stage inverter based on cuk converter
KR20220106511A (en) 2021-01-22 2022-07-29 전북대학교산학협력단 Bidirectional Isolated Inverter circuit and Energy Storage System using the same
KR20230019566A (en) * 2021-08-02 2023-02-09 한국에너지기술연구원 Power conversion system for salinity gradient power generation
KR102573283B1 (en) 2021-08-02 2023-09-06 한국에너지기술연구원 Power conversion system for salinity gradient power generation

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