JPWO2019244244A1 - Phaser - Google Patents

Abstract

A high frequency filter (100) connected between the first output end (3b) of the input side changeover switch (3) and the first input end (4a) of the output side changeover switch (4), and an input side. A right-handed / left-handed composite line (200) connected between the second output end (3c) of the changeover switch (3) and the second input end (4b) of the output side changeover switch (4) is provided.

Description

The present invention relates to a phase shifter, and more particularly to a phase shifter having a structure for switching between a high frequency filter and a right-hand / left-hand composite line (CRLH line) with a switch.

As a phase shifter, for example, in Patent Document 1, a T-type high-frequency filter and a T-type or π-type low-frequency filter are switched and connected between an input terminal and an output terminal by an input side changeover switch and an output side changeover switch. The phase shifter is shown.
In the phase shifter configured in this way, the high frequency filter causes a phase lead, and the low frequency filter causes a phase lag. As a result, a passing phase difference is generated by switching the high frequency filter and the low frequency filter between the high frequency filter and the low frequency filter by the input side changeover switch and the output side changeover switch, and the phase shift amount is obtained from this passing phase difference. ..

JP-A-2002-76810

In a phase shifter that switches and connects a high-frequency filter and a low-frequency filter, the high-frequency filter has the characteristics of a large phase shift advance in the low-frequency region and a small transfer advance in the high-frequency region, and has low-frequency The filter has a phase lag characteristic in which the phase lag is small in the low frequency region and the phase lag is large in the high frequency region.
As a result, the passing phase difference due to switching between the high frequency filter and the low frequency filter by the input side changeover switch and the output side changeover switch has a phase shift amount error in the low frequency region with respect to the set phase shift amount, and the transfer in the high frequency region. There is a problem that it becomes large with respect to the quantity error and it is difficult to obtain the range of the phase shift amount error set for the set phase shift amount over a wide frequency region.

The present invention has been made in view of the above-mentioned problems, and a phase shifter capable of reducing the phase shift amount error in the low frequency region with respect to the phase shifter for switching and connecting the conventional high frequency filter and low frequency filter. The purpose is to get.

The phase shifter according to the present invention has an output having a first output end of an input side changeover switch having a first output end and a second output end, and an output having a first input end and a second input end. A high-frequency filter connected between the first input end of the side changeover switch, and a right hand connected between the second output end of the input side changeover switch and the second input end of the output side changeover switch.・ Equipped with a left-handed composite line.

According to the present invention, the phase shift amount error in the high frequency region can be made smaller than that of the phase shifter that switches and connects the conventional high frequency filter and low frequency filter.

It is a circuit diagram which shows the phase shifter which concerns on Embodiment 1 of this invention. It is a figure which shows the relationship between the frequency and the passing phase of the high region filter and the right-handed-left-handed composite line in the phase shifter which concerns on Embodiment 1 of this invention. It is an equivalent circuit diagram at the time of low frequency operation of the right-handed-left-handed composite line in the phase shifter which concerns on Embodiment 1 of this invention. It is an equivalent circuit diagram at the time of high frequency operation of the right-handed-left-handed composite line in the phase shifter which concerns on Embodiment 1 of this invention. It is a figure which shows the relationship between the frequency and the passing phase in the phase shifter which concerns on Embodiment 1 of this invention. It is a figure which shows the result of having verified the relationship between the frequency and the passing phase of the high region filter and the right-handed-left-handed composite line in the phase shifter which concerns on Embodiment 1 of this invention. It is a figure which shows the result of having verified the relationship between the frequency and the passing phase of the high region filter and the right-handed-left-handed composite line in the phase shifter which concerns on Embodiment 1 of this invention. It is a circuit diagram which shows the phase shifter which concerns on Embodiment 2 of this invention. It is a circuit diagram which shows the phase shifter which concerns on Embodiment 3 of this invention. It is a circuit diagram which shows the phase shifter which concerns on Embodiment 4 of this invention. It is a circuit diagram which shows the phase shifter which concerns on Embodiment 5 of this invention. It is a circuit diagram which shows the phase shifter which concerns on Embodiment 6 of this invention. It is a circuit diagram which shows the phase shifter which concerns on Embodiment 7 of this invention.

Hereinafter, in order to explain the present invention in more detail, a mode for carrying out the present invention will be described with reference to the accompanying drawings.
Embodiment 1.
The phase shifter according to the first embodiment of the present invention will be described with reference to FIGS. 1 to 7.
FIG. 1 is a diagram showing a phase shifter according to the first embodiment of the present invention.
In FIG. 1, a high frequency signal is input to the input terminal 1. A high-frequency signal is output from the output terminal 2, and the amount of phase shift is obtained from the passing phase difference caused by the high-frequency signal that has passed by switching between the two transmission paths.

The input side changeover switch 3 has an input terminal 3a connected to the input terminal 1, a first output terminal 3b, and a second output terminal 3c. The input side changeover switch 3 is composed of, for example, the SPDT switch 4 shown in Patent Document 1.
The output side changeover switch 4 has a first input terminal 4a, a second input terminal 4b, and an output terminal 4c connected to the output terminal 2. The output side changeover switch 4 is composed of, for example, the SPDT switch 5 shown in Patent Document 1.
The input side changeover switch 3 and the output side changeover switch 4 are switches that can be switched to a changeover signal (not shown). When the changeover signal indicates high frequency selection, the input side changeover switch 3 connects the input end 3a and the first output end 3b, and the output side changeover switch 4 connects the first input end 4a and the output end 4c.
Further, when the changeover signal indicates low frequency selection, the input side changeover switch 3 connects the input end 3a and the second output end 3c, and the output side changeover switch 4 connects the second input end 4b and the output end 4c. To do.

The high frequency filter 100 is connected between the first output terminal 3b of the input side changeover switch 3 and the first input end 4a of the output side changeover switch 4.
The high frequency filter 100 is placed between the first output terminal 3b of the input side changeover switch 3 and the first input end 4a of the output side changeover switch 4 in order from the first output end 3b side of the input side changeover switch 3. Between the first high-frequency capacitance 101 and the second high-frequency capacitance 102 connected in series, and the connection point P1 and the grounding node of the first high-frequency capacitance 101 and the second high-frequency capacitance 102. It has a first high frequency inductor 103 connected to.

The capacitance CH of the first high-frequency capacitance 101 and the second high-frequency capacitance 102 constituting the high-frequency filter 100 and the inductance LH of the first high-frequency inductor 103 are the following equations (1) and the following equations, respectively. Shown in (2).
As can be understood from these equations (1) and (2), the capacitance CH of the first high-frequency capacitance 101 and the second high-frequency capacitance 102 constituting the high-frequency filter 100, and the first high. The inductance LH of the regional inductor 103 depends on the operating center frequency ω0 and the passing phase Φ0.

That is, the capacitance CH of the first high-frequency capacitance 101 and the second high-frequency capacitance 102 constituting the high-frequency filter 100 has a standardized susceptance of the operating center frequency ω0, which is half of the phase shift amount (passing phase) Φ0. The relationship satisfies the reciprocal of the tangent of. FIG. 2 shows the relationship between the operating center frequency ω0 and the passing phase Φ0.
Further, the inductance LH of the first high frequency inductor 103 constituting the high frequency filter 100 has a relationship in which the normalized reactance of the center frequency satisfies the reciprocal of the sine of the phase shift amount.
The operating center frequency of the high frequency filter 100 is set to the operating center frequency ω0 of the phase shifter.

但し、ω0は動作中心周波数の角周波数、Ｚ0は給電回路系インピーダンス、Φ0は動作中心周波数ω0における高域フィルタ１００の通過位相である。

However, ω0 is the angular frequency of the operating center frequency, Z0 is the feeding circuit system impedance, and Φ0 is the passing phase of the high frequency filter 100 at the operating center frequency ω0.

The high frequency filter 100 has a phase shift advance characteristic as shown by the characteristic curve C1 in FIG. FIG. 2 is a diagram showing the relationship between frequency and passing phase. The horizontal axis indicates the frequency, the vertical axis indicates the passing phase, the upper axis indicates the phase lead, and the lower axis indicates the phase lag. As can be understood from the characteristic curve C1 of FIG. 2, it shows a characteristic that the phase shift advance is large in the low frequency region and a characteristic that the transfer advance is small in the high frequency region.

The right-handed / left-handed composite line (hereinafter referred to as CRLH line) 200 is connected between the second output terminal 3c of the input side changeover switch 3 and the second input end 4b of the output side changeover switch 4.
The CRLH line 200 is placed between the second output end 3c of the input side changeover switch 3 and the second input end 4b of the output side changeover switch 4 in order from the second output end 3c side of the input side changeover switch 3. The first low frequency inductor 201 and the first low frequency capacitance 202 connected in series, and the second low frequency connected in parallel between the second input terminal 4b of the output side changeover switch 4 and the ground node. It has a region capacitance 203 and a second low frequency inductor 204.

The inductance LR of the first low-frequency inductor 201 constituting the CRLH line 200 is set to the following equation (3), the capacitance CL of the first low-frequency capacitance 202 is set to the following equation (4), and the second low-frequency inductor is used. The inductance LL of the inductor 204 is shown in the following equation (5), and the capacitance CR of the second low-frequency capacitance 203 is shown in the following equation (6).
Further, the coefficients A and β used in the equations (3) to (6) are shown in the following equations (7) and (8), respectively.
In the first embodiment, as will be described later, the boundary frequency ωγ during operation in the low frequency region and operation in the high frequency region is set as the operation center frequency ω0 of the phase shifter. As a result, the operating center frequency of the high frequency filter 100 and the operating center frequency of the CRLH line 200 coincide with the operating center frequency ω0 of the phase shifter.

As can be understood from these equations (4) to (6), the capacitance CL of the first low-frequency capacitance 202 constituting the CRLH line 200, the inductance LL of the second low-frequency inductor 204, and the first The capacitance CR of the low frequency capacitance 203 of 2 depends on the inductance LR of the first low frequency inductor 201.
Further, as can be understood from the equation (3), since the inductance LR of the first low-pass inductor 201 depends on the operating center frequency ω0, the capacitance CL of the first low-pass capacitance 202 and The inductance LL of the second low-pass inductor 204 and the capacitance CR of the second low-pass capacitance 203 also depend on the operating center frequency ω0.
Further, as can be understood from the equations (7) and (8), since the coefficient β depends on the frequency bandwidth, the bandwidth of the phase shifter is the first low-pass inductor constituting the CRLH line 200. It depends on the inductance LR of 201, the capacitance CL of the first low-frequency capacitance 202, the inductance LL of the second low-frequency inductor 204, and the capacitance CR of the second low-frequency capacitance 203.
As can be understood from Eqs. (7) and (8), Lmim has a passing amplitude of Lmim or more at the operating lower limit frequency ωmim.

但し、ωmimとωmaxはそれぞれCRLH線路２００における動作下限動作周波数と動作上限周波数の角周波数である。

However, ωmim and ωmax are the angular frequencies of the operating lower limit operating frequency and the operating upper limit frequency on the CRLH line 200, respectively.

In the CRLH line 200, in the low frequency region, the first low frequency inductor 201 and the first low frequency capacitance 202 connected in series are dominated by the first low frequency capacitance 202 and are connected in parallel. In the low-frequency capacitance 203 and the second low-frequency inductor 204 of 2, the second low-frequency inductor 204 becomes dominant. Therefore, the CRLH line 200 functions as a high-frequency filter composed of a first low-frequency capacitance 202 and a second low-frequency inductor 204 in operation in the low-frequency region as shown in FIG. 3, and exhibits phase lead characteristics. Behave as if you have it.

On the other hand, in the high frequency region, the CRLH line 200 is connected in parallel with the first low-frequency inductor 201 and the first low-frequency capacitance 202 connected in series so that the first low-frequency inductor 201 dominates. In the low frequency capacitance 203 and the second low frequency inductor 204 of 2, the second low frequency capacitance 203 becomes dominant. Therefore, the CRLH line 200 functions as a low-frequency filter composed of the first low-frequency inductor 201 and the second low-frequency capacitance 203 as shown in FIG. 4 during operation in the high-frequency region, and exhibits phase lag characteristics. Behave as if you have it.

Further, in the first embodiment, since there is no band gap that is neither during operation in the low frequency region nor during operation in the high frequency region, the first low frequency inductor 201 and the first are connected in series. The resonance frequency ωse of the low-frequency capacitance 202 and the resonance frequency ωsh of the second low-frequency capacitance 203 and the second low-frequency inductor 204 connected in parallel are the same.

That is, assuming that the boundary frequency (Γ point frequency) ωγ during operation in the low frequency region and operation in the high frequency region, the CRLH line 200 operates in the low frequency region and in the high frequency region with respect to the boundary frequency ωγ. The condition for not having a bandgap that is neither of the times is ωγ = ωse = ωsh.
When the boundary frequency ωγ matches the resonance frequency ωse and the resonance frequency ωsh, the second low frequency band connected in parallel with the series resonance by the first low frequency inductor 201 and the first low frequency capacitance 202 connected in series. The passing phase of the CRLH line 200 becomes 0 due to the parallel resonance of the capacitance 203 and the second low-pass inductor 204.
Therefore, the boundary frequency ωγ is set to the operating center frequency ω0 of the phase shifter.

Therefore, the CRLH line 200 behaves as a high frequency filter in the low frequency region, acts as a low frequency filter in the high frequency region, sets the boundary frequency ωγ to the operating center frequency ω0 of the phase shifter, and sets the passing phase at the boundary frequency ωγ. Since it is set to 0, as shown by the characteristic curve C2 in FIG. 2, it has a phase lead characteristic in a low frequency region lower than the boundary frequency ωγ, and a phase delay characteristic in a high frequency region higher than the boundary frequency ωγ. Have.
Further, as can be understood from the characteristic curve C1 and the characteristic curve C2 in FIG. 2, the passing phase difference between the two curves C1-C2 can be substantially the same from the low frequency region to the high frequency region.

In the first embodiment, the amount of phase shift from the phase shifter is the characteristic curve C0 shown in FIG. FIG. 5 is a diagram showing the relationship between the frequency and the amount of phase shift. The horizontal axis shows the frequency and the vertical axis shows the amount of phase shift. The operating center frequency ω0 of the phase shifter is the operating center frequency FC, the phase shifting amount at the operating center frequency FC is Φ0, and the high frequency FH, that is, the transfer amount error with the phase shifting amount Φ0 at the operating upper limit frequency ωmax of the CRLH line 200 is A. , Low frequency FL, that is, the transfer amount error with the phase shift amount Φ0 at the operation lower limit frequency ωmim of the CRLH line 200 is shown by B1. For comparison, the characteristic curve of the phase shifter that switches and connects the conventional high-frequency filter and low-frequency filter is shown as Cc.

As can be understood from FIG. 5, the operating center frequency FC, that is, the phase shift amount Φ0 at the operating center frequency ω0 of the phase shifter has a passing phase of Φ0 at the operating center frequency ω0 of the high frequency filter 100, and the CRLH line 200. Since the passing phase of is 0, it becomes the same as the passing phase Φ0 at the operating center frequency ω0 of the high frequency filter 100.
The phase shift amount Φ0 at the operating center frequency ω0 of the phase shifter is the phase shift amount of the phase shifter.
Then, the transfer amount error B1 with the phase shift amount Φ0 in the low frequency FL in the phase shifter according to the first embodiment can be made substantially the same as the transfer amount error A with the phase shift amount Φ0 in the high frequency FH, and the conventional transfer It can be reduced from the transfer amount error B2 with the phase shift amount PSH in the low frequency FL in the phase unit.
As a result, the phase shift amount error in the phase shifter can be suppressed to be low within a wide frequency range from low frequency FL to high frequency FH. As a result, the phase shifter shown in the first embodiment has a flat phase shift amount characteristic over a wide frequency band, so that a wide band phase shifter can be realized.

In the phase shifter configured as described above, using a microwave circuit simulator (Microwave Office, NI AWR), the relationship between the frequency and the passing phase in the high frequency filter 100, and the frequency and the passing phase in the CRLH line 200. The results of verifying the relationship between the above and the frequency as a phase shifter and the phase shift amount are shown in FIGS. 6 and 7.
The verification is performed by setting the design value in a phase shift amount of 45 ° and a quadruple band (4 to 16 GHz).
As shown in FIG. 6, the characteristic curve C1 in the high frequency filter 100 and the characteristic curve C2 in the CRLH line 200 have substantially the same change in passing phase from 4 GHz to 19 GHz.
As a result, as shown in FIG. 7, the characteristic curve C0 of the phase shifter shows a flat phase shift amount characteristic from 4 GHz to 19 GHz.
As is clear from the above, since the phase shifter according to the first embodiment has a flat phase shift amount characteristic over a wide frequency band, a wide band phase shifter can be realized.

Embodiment 2.
Embodiment 2 of the present invention will be described with reference to FIG.
The phase shifter according to the second embodiment of the present invention is the same as the phase shifter according to the first embodiment in that the high frequency filter 100 is changed to the high frequency filter 100a, and the other points are the same. is there. In FIG. 8, the same reference numerals as those shown in FIG. 1 indicate the same or corresponding portions.
Therefore, the high frequency filter 100a will be mainly described.

The high frequency filter 100a is serialized between the first output end 3b of the input side changeover switch 3 and the first input end 4a of the output side changeover switch 4 in order from the first output end 3b of the input side changeover switch 3. A second high-frequency inductor 104, a first high-frequency capacitance 101, a second high-frequency capacitance 102, a third high-frequency inductor 105, and these first high-frequency capacitance 101 are connected. It has a first high frequency inductor 103 connected between the connection point P1 of the second high frequency capacitance 102 and the grounding node.

That is, the high frequency filter 100a configured in this way has the first output terminal 3b and the first high frequency of the input side changeover switch 3 with respect to the high frequency filter 100 shown in the first embodiment. A third inductor 104 connected between the second high frequency inductor 104 and the second high frequency inductor 104, and a third input terminal 4a of the second high frequency capacitance 102 and the output side changeover switch 4. The high frequency inductor 105 is provided.

The high-frequency filter 100a configured in this way uses the second high-frequency inductor 104 and the third high-frequency inductor 105 to form the second high-frequency inductor 104 and the third high-frequency inductor 105. The phase lead becomes smaller in the high frequency region than the one not provided.
Therefore, in the high frequency region, the passing phase difference can be reduced with respect to the phase delay of the CRLH line 200. As a result, as the phase shifter, the transfer amount error in the high frequency region can be reduced, the flat phase shift amount characteristic in the high frequency region can be widely obtained, and a wide band phase shifter can be realized.

In the second embodiment, both the second high-frequency inductor 104 and the third high-frequency inductor 105 are provided, but the second high-frequency inductor 104 and the third high-frequency inductor 104 are provided. Any one of the inductors 105 may be provided.
The second high-frequency inductor 104 or the third high-frequency inductor 105 causes the phase lead in the high-frequency region with respect to the one without the second high-frequency inductor 104 and the third high-frequency inductor 105. It becomes smaller.
As a result, the same effect as that of the second embodiment can be obtained.

Embodiment 3.
Embodiment 3 of the present invention will be described with reference to FIG.
The phase shifter according to the third embodiment of the present invention is the same as the phase shifter according to the first embodiment in that the high frequency filter 100 is changed to the high frequency filter 100b, and the other points are the same. is there. In FIG. 9, the same reference numerals as those shown in FIG. 1 indicate the same or corresponding portions.
Therefore, the high frequency filter 100b will be mainly described.

The high frequency filter 100b is placed between the first output end 3b of the input side changeover switch 3 and the first input end 4a of the output side changeover switch 4 in order from the first output end 3b side of the input side changeover switch 3. Between the first high-frequency capacitance 101 and the second high-frequency capacitance 102 connected in series, and the connection point P1 and the ground node of the first high-frequency capacitance 101 and the second high-frequency capacitance 102. The first high-frequency inductor 103 connected to the first high-frequency inductor 103, the first high-frequency resistor 106 connected in parallel to the first high-frequency capacitance 101, and the second high-frequency capacitance 102 connected in parallel. It has a second high frequency resistor 107.

That is, the high frequency filter 100b configured in this way is connected to the high frequency filter 100 shown in the first embodiment in parallel with the first high frequency capacitance 101. A resistance 106 and a second high-frequency resistor 107 connected in parallel to the second high-frequency capacitance 102 are provided.

The high frequency filter 100b configured in this way can increase the passing loss in the high frequency filter 100b by providing the first high frequency resistor 106 and the second high frequency resistor 107. As a result, the pass loss of the high frequency filter 100b and the CRLH line 200 can be made the same.
Therefore, the phase shifter according to the third embodiment has the same effect as the phase shifter according to the first embodiment, and when the phase shifter is used for the array antenna, the deterioration of the array antenna can be prevented. It has the effect of being able to do it.

Embodiment 4.
Embodiment 4 of the present invention will be described with reference to FIG.
The phase shifter according to the fourth embodiment of the present invention is the same as the phase shifter according to the first embodiment in that the high frequency filter 100 is changed to the high frequency filter 100c, and the other points are the same. is there. In FIG. 10, the same reference numerals as those shown in FIG. 1 indicate the same or corresponding portions.
Therefore, the high frequency filter 100c will be mainly described.

The high frequency filter 100c is placed between the first output end 3b of the input side changeover switch 3 and the first input end 4a of the output side changeover switch 4 in order from the first output end 3b side of the input side changeover switch 3. Between the first high-frequency capacitance 101 and the second high-frequency capacitance 102 connected in series, and the connection point P1 and the grounding node of the first high-frequency capacitance 101 and the second high-frequency capacitance 102. A first high-frequency inductor 103 and a third high-frequency resistor 108 are connected in series from the connection point P1 side.

That is, the high frequency filter 100c configured in this way is connected to the high frequency filter 100 shown in the first embodiment further between the first high frequency inductor 103 and the ground node. The high frequency resistor 108 of 3 is provided.

The high frequency filter 100c configured in this way can increase the pass loss in the high frequency filter 100c by providing the third high frequency resistor 108. As a result, the pass loss of the high frequency filter 100c and the CRLH line 200 can be made the same.
Therefore, the phase shifter according to the fourth embodiment has the same effect as the phase shifter according to the first embodiment, and when the phase shifter is used for the array antenna, the deterioration of the array antenna can be prevented. It has the effect of being able to do it.

Embodiment 5.
Embodiment 5 of the present invention will be described with reference to FIG.
The phase shifter according to the fifth embodiment of the present invention is the same as the phase shifter according to the first embodiment in that the CRLH line 200 is changed to the CRLH line 200a, and the other points are the same. In FIG. 11, the same reference numerals as those shown in FIG. 1 indicate the same or corresponding portions.
Therefore, the CRLH line 200a will be mainly described.

The CRLH line 200a is a so-called π-type CRLH line, and is a second input side changeover switch 3 between the second output end 3c of the input side changeover switch 3 and the second input end 4b of the output side changeover switch 4. The first low-frequency inductor 201 and the first low-frequency capacitance 202, which are connected in series from the output end 3c side of the output side, and the second input terminal 4b of the output side changeover switch 4 and the ground node are connected in parallel. The second low-frequency capacitance 203 and the second low-frequency inductor 204, and the third low-frequency capacitance connected in parallel between the second output end 3c of the input side changeover switch 3 and the ground node. It has 205 and a third low frequency inductor 206.

That is, the CRLH line 200a configured in this way is further connected in parallel to the CRLH line 200 shown in the first embodiment between the second output terminal 3c of the input side changeover switch 3 and the ground node. A third low-frequency capacitance 205 and a third low-frequency inductor 206 are provided.

The CRLH line 200a configured in this way is provided by the third low-frequency capacitance 205 and the third low-frequency inductor 206 connected in parallel, thereby using the third low-frequency capacitance 205 and the third low-frequency inductor 206. The phase lag is smaller in the high frequency region than the one without the inductor 206.
Therefore, in the high frequency region, the passing phase difference can be reduced with respect to the phase delay of the high frequency filter 100. As a result, as the phase shifter, the transfer amount error in the high frequency region can be reduced, the flat phase shift amount characteristic in the high frequency region can be widely obtained, and a wide band phase shifter can be realized.

Embodiment 6.
Embodiment 6 of the present invention will be described with reference to FIG.
The phase shifter according to the sixth embodiment of the present invention is the same as the phase shifter according to the first embodiment in that the CRLH line 200 is changed to the CRLH line 200b, and the other points are the same. In FIG. 12, the same reference numerals as those shown in FIG. 1 indicate the same or corresponding portions.
Therefore, the CRLH line 200b will be mainly described.

The CRLH line 200b is serially connected between the second output terminal 3c of the input side changeover switch 3 and the second input end 4b of the output side changeover switch 4 from the second output end 3c side of the input side changeover switch 3. Between the first low frequency resistor 207, the first low frequency inductor 201, and the first low frequency capacitance 202 to be connected, and the second input end 4b of the output side changeover switch 4 and the ground node. It has a second low-frequency capacitance 203 and a second low-frequency inductor 204 connected in parallel.

That is, the CRLH line 200b configured in this way has the second output terminal 3c of the input side changeover switch 3 and the first low frequency inductor with respect to the CRLH line 200 shown in the first embodiment. The first low-pass resistor 207 connected between 201 is provided.

The CRLH line 200b configured in this way can increase the passing loss of the CRLH line 200b by providing the first low frequency resistor 207. As a result, the pass loss of the high frequency filter 100 and the CRLH line 200b can be made the same.
Therefore, the phase shifter according to the sixth embodiment has the same effect as the phase shifter according to the first embodiment, and when the phase shifter is used for the array antenna, the deterioration of the array antenna can be prevented. It has the effect of being able to do it.

Embodiment 7.
Embodiment 7 of the present invention will be described with reference to FIG.
The phase shifter according to the seventh embodiment of the present invention is the same as the phase shifter according to the first embodiment in that the CRLH line 200 is changed to the CRLH line 200c, and the other points are the same. In FIG. 12, the same reference numerals as those shown in FIG. 1 indicate the same or corresponding portions.
Therefore, the CRLH line 200c will be mainly described.

The CRLH line 200c is serially connected between the second output end 3c of the input side changeover switch 3 and the second input end 4b of the output side changeover switch 4 from the second output end 3c side of the input side changeover switch 3. The first low-pass inductor 201 and the first low-pass capacitance 202 to be connected, and the second low-pass capacitance 202 connected in parallel between the second input terminal 4b of the output side changeover switch 4 and the ground node. It has a capacitance 203 and a second low-frequency inductor 204, and a second low-frequency resistor 208 connected in parallel with a second low-frequency capacitance 203 and a second low-frequency inductor 204 connected in parallel.

That is, the CRLH line 200c configured in this way has a second low-frequency capacitance 203 and a second low-frequency inductor connected in parallel with the CRLH line 200 shown in the first embodiment. A second low-pass resistor 208, which is connected in parallel with the 204, is provided.

The CRLH line 200c configured in this way can increase the passing loss of the CRLH line 200c by providing the second low frequency resistor 208. As a result, the pass loss of the high frequency filter 100 and the CRLH line 200c can be made the same.
Therefore, the phase shifter according to the seventh embodiment has the same effect as the phase shifter according to the first embodiment, and when the phase shifter is used for the array antenna, deterioration of the array antenna can be prevented. It has the effect of being able to do it.

It should be noted that, within the scope of the present invention, it is possible to freely combine each embodiment, modify any component of each embodiment, or omit any component in each embodiment. ..

The phase shifter according to the present invention is particularly suitably applicable to a phased array antenna and a multi-beam antenna.

1 input terminal, 2 output terminal, 3 input side changeover switch, 3a input end, 3b first output end, 3c second output end, 4 output side changeover switch, 4a first input end, 4b second input End, 4c output end, 100, 100a, 100b, 100c, high frequency filter, 101 first high frequency capacitance, 102 second high frequency capacitance, 103 first high frequency inductor, 104 second high Inductor for region, 105 Inductor for third high frequency, 106 First high frequency resistor, 107 Second high frequency resistor, 108 Third high frequency inductor, 200, 200a, 200b, 200c, CRLH line , 201 1st low frequency inductor, 202 1st low frequency capacitance, 203 2nd low frequency capacitance, 204 2nd low frequency inductor, 205 3rd low frequency capacitance, 206 3rd Low frequency inductor, 207 1st low frequency resistor, 208 2nd low frequency resistor.

Claims (14)

A first output end of an input side changeover switch having a first output end and a second output end, and a first input end of an output side changeover switch having a first input end and a second input end. High frequency filter connected between
A phase shifter including a right-handed / left-handed composite line connected between the second output end of the input-side changeover switch and the second input end of the output-side changeover switch. The high frequency filter is
A first high-frequency capacitance and a second high-frequency capacitance connected in series between the first output end of the input-side changeover switch and the first input end of the output-side changeover switch.
The phase shifter according to claim 1, further comprising a first high-pass inductor connected between the connection point of the first high-pass capacitance and the second high-pass capacitance and the ground node. .. The high frequency filter is
The capacitances of the first high-frequency capacitance and the second high-frequency capacitance have a relationship in which the normalized susceptance of the operating center frequency satisfies the reciprocal of the tangent of half the phase shift amount.
The phase shifter according to claim 2, wherein the inductance of the first high-pass inductor is such that the normalized reactance of the operating center frequency satisfies the reciprocal of the sine of the phase shift amount. The high frequency filter is
For the second high frequency range, which is connected in series between the first output end of the input side changeover switch and the first input end of the output side changeover switch from the first output end of the input side changeover switch. The inductor, the first high frequency capacitance, and the second high frequency capacitance,
The phase shifter according to claim 1, further comprising a first high-pass inductor connected between the connection point of the first high-pass capacitance and the second high-pass capacitance and the ground node. .. The high frequency filter is
For the first high frequency range, which is connected in series between the first output end of the input side changeover switch and the first input end of the output side changeover switch from the first output end of the input side changeover switch. Capacitance, second high frequency capacitance, and third high frequency inductor,
The phase shifter according to claim 1, further comprising a first high-pass inductor connected between the connection point of the first high-pass capacitance and the second high-pass capacitance and the ground node. .. The high frequency filter is
For the second high region connected in series from the first output end of the input side changeover switch between the first output end of the input side changeover switch and the first input end of the output side changeover switch. An inductor, a first high frequency capacitance, a second high frequency capacitance, and a third high frequency inductor,
The phase shifter according to claim 1, further comprising a first high-pass inductor connected between the connection point of the first high-pass capacitance and the second high-pass capacitance and the ground node. .. The high frequency filter is
A first high-frequency resistor connected in parallel to the first high-frequency capacitance,
The phase shifter according to any one of claims 1 to 6, further comprising a second high frequency resistor connected in parallel to the second high frequency capacitance. The high-frequency filter according to any one of claims 1 to 7, wherein the high-frequency filter has a third high-frequency resistor connected between the first high-frequency inductor and the ground node. The described phase shifter. The right-handed / left-handed composite line is
A first low-pass inductor and a first low-pass capacitance connected in series between the second output end of the input-side changeover switch and the second input end of the output-side changeover switch.
Claims 1 to 8 include a second low-pass capacitance and a second low-pass inductor that are connected in parallel between the second input end of the output-side changeover switch and the ground node. The phase shifter according to any one of the above. The resonance frequencies of the first low-frequency inductor and the first low-frequency capacitance connected in series are the same as the resonance frequencies of the second low-frequency capacitance and the second low-frequency inductor connected in parallel. The phase shifter according to claim 9, wherein the phase transfer device is characterized by the above. The right-handed / left-handed composite line is
The phase shift according to claim 9, further comprising a third low-pass capacitance and a third low-pass inductor that are connected in parallel between the second output end of the input-side changeover switch and the ground node. vessel. The right-handed / left-handed composite line is
The first low-pass inductor and the first low-pass capacitance are connected in series from the second output end of the input-side changeover switch.
Further, claim 9 or 11, further comprising a first low-pass resistor connected between the second output end of the input-side changeover switch and the first low-pass inductor. The described phase shifter. The claim is characterized in that the right-handed / left-handed composite line has a second low-frequency capacitance connected in parallel and a second low-frequency resistor connected in parallel with the second low-frequency inductor. 9. The phase shifter according to any one of claims 11 or 12. A first output end of an input side changeover switch having a first output end and a second output end, and a first input end of an output side changeover switch having a first input end and a second input end. A high-frequency filter, which is connected between the two, has a passing phase Φ0 at the center frequency of operation, and has a phase shift lead characteristic.
It is connected between the second output end of the input side changeover switch and the second input end of the output side changeover switch, has a phase lead characteristic during operation in the low frequency region, and operates in the high frequency region. Time has a phase lag characteristic, and the passing phase at the boundary frequency between the operation in the low frequency region and the operation in the high frequency region is 0, and the boundary frequency is the operation center frequency. A phase shifter with a composite line.

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