JPH09182482A - Brushless motor - Google Patents

Abstract

PROBLEM TO BE SOLVED: To lessen the influence even in case that dispersion occurs in the amplitude of the detection signal of a Hall element or the like by making a distribution signal by the multiplication result of the output signal of a command signal and the corrected output signal of a switching making means, and supplying a drive signal. SOLUTION: This brushless motor makes out a corrective signal which changes in proportion to the amplitude of the detection signal of a position detector 4021, and corrects the amplitude of the output signal of a switching maker 4022 into one corresponding the specified signal. This makes out a distribution signal by the multiplication result of this corrected output signal of the switching maker 4022 and the output signal of a command current apparatus 4050. Accordingly, the amplitude of the output signal of the switching maker 4022 and the amplitude of the distribution signal of a distributor 4031 cease to be influenced by the amplitude of the detection signal of the position detector 4021. As a result, the drive signal supplied to a three-phase coil ceases to be affected by the dispersion in detection of the position detector 4021, and the dispersion of relation between the command signal and the generated torque ceases to occur.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a brushless motor for detecting the position of a motor and energizing a coil.

[0002]

2. Description of the Related Art In recent years, brushless motors have been used in which the rotational position of a motor is detected by a hall element and the energization of a three-phase coil is switched according to the detected output. Fig. 78
Figure 1 shows the configuration of a conventional brushless motor. The magnetic poles of the rotor rotating magnet 9901 are used as hall elements 9911, 9912, 9
913 detects and outputs a three-phase detection signal according to the rotational position. Hall elements 9911, 9912, 9913
The outputs of the amplifiers are amplifiers 9921, 9922, and 992, respectively.
Amplification by a predetermined number is performed by 3. Multiplier 9931, 9
932 and 9933 are amplifiers 9921 and 992, respectively.
The output of 2,9923 is multiplied by the command signal of the command device 9950 to obtain a three-phase multiplication signal having an amplitude in response to the command signal.
The power amplifiers 9941, 9942 and 9943 are multipliers 9
A drive signal having a voltage waveform obtained by proportionally amplifying the outputs of 931, 9932, and 9933 is converted into a three-phase coil 9902, 9903, 9
904. As a result, a three-phase drive signal that changes with the rotation of the rotor magnet 9901 is applied to the three-phase coil 990.
2,9903,9904, rotor magnet 990
1 keeps rotating in a predetermined direction.

[0003]

However, the above-mentioned conventional configuration has the following problems. The amplitude of the drive signal applied to the coil is proportional to the multiplication result of the command signal of the command device 9950 and the detection signals of the Hall elements 9911, 9912, 9913. Variations in the detection signals of the Hall elements 9911, 9912, and 9913 occur due to variations in the sensitivity of the Hall elements and variations in the magnetic field of the rotor magnet 9901, resulting in variations in the voltage amplitude of the drive signal that is the multiplication result. Especially, the sensitivity variation of the Hall element is very large, and the amplitude variation of the Hall element output causes the large amplitude variation of the drive signal. Conventionally, the three Hall elements in the individual motors are matched so that the sensitivity ranges of the Hall elements are the same, so that the influence of relative sensitivity variations is reduced. However, between motors during mass production, large amplitude fluctuations of the drive signal remained due to sensitivity fluctuations of the Hall element. This variation in amplitude causes variation in the torque generated by the motor with respect to the command signal from the command device 9950, which has been a serious problem in using the brushless motor. For example, when performing speed control of a brushless motor, variations in control gain occur, which causes instability in control. Further, when the torque control of the brushless motor is performed, the generated torque amount varies, and accurate control is difficult. An object of the present invention is to solve the above-mentioned conventional problems, and to provide a brushless motor in which the influence of the amplitude variation of the detection signal of the Hall element or the like is extremely small even if the variation occurs.

[0004]

In order to achieve this object, the brushless motor of the first type of the present invention comprises field means for obtaining a field flux by the magnetic flux generated by the permanent magnet magnetic poles.
A three-phase coil interlinking with the field magnetic flux, and position detecting means for detecting the relative position of the field means and the three-phase coil,
A switching creating means for obtaining a three-phase output signal that smoothly changes in response to the output signal of the position detecting means, and a correction signal that changes in proportion to the amplitude of the detection signal of the position detecting means are created. And a predetermined signal for comparing the amplitude of the output signal of the switching creating means, a commanding means for obtaining an output signal in response to the command signal, an output signal of the commanding means and an output of the switching creating means. Distribution means for obtaining a three-phase distribution signal that smoothly changes in response to the result of signal multiplication, and a power-amplified drive signal that responds to the three-phase distribution signals of the distribution means and is supplied to the three-phase coil. And a driving means.

Further, in the brushless motor of the second type of the present invention, field means for obtaining a field magnetic flux by the magnetic flux generated by the permanent magnet magnetic poles, a three-phase coil interlinking with the field magnetic flux, and Position detecting means for detecting the relative position of the field means and the three-phase coil, switching generating means for obtaining a three-phase current signal that smoothly changes in response to the output signal of the position detecting means, and the switching generating means. A correction signal that changes in accordance with the addition value of the unipolar values or the addition value of the absolute values of the three-phase current signals is generated, and the amplitude of the output signal of the switching generation means is compared by comparing the correction signal with a predetermined signal. Switching correction means for correcting, command means for obtaining an output signal in response to the command signal, and three-phase distribution signal that changes smoothly in response to the multiplication result of the output signal of the command means and the output signal of the switching creation means. Distributor to get If, in response to distributed signals of three phases of the distribution means, in which the driving signal is power-amplified and configured by including a drive means for supplying to the three-phase coils.

Further, in the brushless motor of the third type of the present invention, field means for obtaining a field flux by the magnetic flux generated by the permanent magnet magnetic pole, a three-phase coil interlinking with the field flux, and Position detection means for detecting the relative position of the field means and the three-phase coil, command means for obtaining an output signal in response to the command signal, and smooth change in response to the output signal of the position detection means Distribution generating means for obtaining a three-phase distribution signal in response to the output signal of the means, and a correction signal that changes in proportion to the amplitude of the detection signal of the position detecting means are generated, and the correction signal and the output signal of the command means are generated. Supplying a drive signal, which is power-amplified in response to the three-phase distribution signals of the distribution compensating means and the distribution compensating means, which substantially corrects the amplitude of the distribution signal of the distribution composing means, to the three-phase coil. Drive means It is constructed by comprising a.

In the brushless motor of the fourth type of the present invention, field means for obtaining a field magnetic flux by the magnetic flux generated by the permanent magnet magnetic pole, a three-phase coil interlinking with the field magnetic flux, and Position detection means for detecting the relative position of the field means and the three-phase coil, command means for obtaining an output signal in response to the command signal, and smooth change in response to the output signal of the position detection means Distribution creating means for obtaining a three-phase distribution signal in response to the output signal of the means, and three-phase current signals in response to the detection signal of the position detecting means, corresponding to the unipolar value added value or the absolute value added value. In response to the three-phase distribution signals of the distribution creating means and the distribution correcting means for compensating the amplitude of the distribution signal by substantially comparing the correction signal with the output signal of the command means. Power is amplified The drive signal is constructed by comprising a driving means for supplying to the three-phase coils.

In the invention of the first type or the second type, a correction signal which changes in proportion to the amplitude of the detection signal of the position detection means is produced, and the switching creation means of the switching generation means is produced according to the comparison result of the correction signal and the predetermined signal. The amplitude of the output signal is corrected to correspond to the predetermined signal. A distribution signal is created by the result of multiplication of the corrected output signal of the switching creation means and the output signal of the command means. Therefore, the amplitude of the output signal of the switching creating means and the amplitude of the distribution signal of the distributing means are not influenced by the amplitude of the detection signal of the position detecting means (the influence of the amplitude is extremely small). As a result, the drive signal supplied to the three-phase coil is not affected by the detection variation of the position detecting means, and the variation of the relationship between the command signal and the generated torque does not occur (extremely small).

In the invention of the third type or the fourth type, a correction signal which changes in proportion to the amplitude of the detection signal of the position detection means is produced, and the distribution preparation means of the distribution generation means is produced based on the comparison result of the correction signal and the predetermined signal. The amplitude of the distribution signal is corrected to correspond to the output signal of the command means. Therefore, the amplitude of the distribution signal of the distribution creating means is not influenced by the amplitude of the detection signal of the position detecting means (the influence of the amplitude is extremely small). As a result, the drive signal supplied to the three-phase coil is not affected by the detection variation of the position detecting means, and the variation of the relationship between the command signal and the generated torque does not occur (extremely small). These and other configurations and operations will be described in detail in the description of the embodiments.

[0010]

BEST MODE FOR CARRYING OUT THE INVENTION Embodiments of the present invention will be described below with reference to the drawings. Embodiment 1 FIGS. 1 to 7 show a brushless motor according to Embodiment 1 of the present invention. FIG. 1 shows an overall configuration diagram. Field part 401 of FIG.
No. 0 is attached to a rotor or a moving body, forms a plurality of field magnetic poles by the magnetic flux generated by the permanent magnet magnetic poles, and generates the field magnetic flux. Three-phase coils 4011A, 401
1B and 4011C are attached to a stator or a fixed body, and are electrically displaced by a predetermined angle (corresponding to 120 degrees) with respect to the linkage with the magnetic flux generated by the field magnet 4010. In addition, the one with a diagonal cross mark on the line in FIG.
Means multiple lines.

FIG. 2 shows a field part 4010 and a three-phase coil 401.
1A, 4011B, and 4011C are specifically shown.
An annular permanent magnet 4102 attached to the inside of the rotor 4101 has four poles on its inner surface and end surface,
The magnetic field portion 4010 of FIG. 1 is formed. Permanent magnet 410
The armature core 4103 at the stator position facing the second magnetic pole.
Are arranged, and the armature core 4103 has three salient pole portions 41.
04a, 4104b and 4104c are mechanically provided at intervals of 120 degrees, and the winding groove 41 is formed between the salient pole portions.
06a, 4106b, 4106c, three-phase coils 4105a, 4105b, 4105c (corresponding to the three-phase coils 4011A, 4011B, 4011C in FIG. 1) are respectively wound around the salient pole portions 4104a, 4104b, 4104c. . Coils 4105a, 4105b, 41
No. 05c is electrically provided with a phase difference of 120 degrees with respect to the interlinkage magnetic flux from the permanent magnet 4102. Where N
A mechanical angle of 180 degrees for one set of pole and S pole corresponds to electrical 360 degrees. The stator has three position detecting elements 4107.
a, 4107b, 4107c (for example, a Hall element that is a magnetoelectric conversion element) are arranged, and the magnetic poles on the end surfaces of the permanent magnets 4102 are detected to detect three phases corresponding to the relative positions of the field magnet portion and the coil. I'm trying to get a signal. By rotating the phase of the coil and the position detection element by 90 degrees in terms of electrical angle, and applying a drive signal of the same phase as the detection signal of the position detection element to the coil, a rotational force in a predetermined direction can be obtained.

The command unit 4015 of FIG. 1 is a command current unit 405.
0, which produces an output current signal in response to the command signal R and supplies it to the distributor 4031 of the distributor 4013. FIG. 3 shows a specific configuration of the command current device 4050. In the circuit to which + Vcc and -Vcc are applied, (+
Vcc = 9V, −Vcc = −9V), transistor 41
21, 4122 and resistors 4123, 4124 form a differential circuit, and in response to the command signal R, the current value of the constant current source 4120 is distributed to the collector side of the transistors 4121, 4122. The collector currents of the transistors 4121 and 4122 are compared by the current mirrors of the transistors 4125 and 4126, and the difference current is calculated.
The output current signal d is obtained by outputting the light through a 128-mirror. Here, when the command signal R becomes smaller than the ground potential 0V, the output current signal d becomes large. The position section 4012 in FIG. 1 is a position detector 4021 and a switching generator 40.
22 and a switching corrector 4023, a switching signal is generated from the detection signal of the position detecting element of the position detector 4021 and supplied to the distributor 4031 of the distributor 4013.

FIG. 4 shows the position detector 4021 and the switching generator 4.
022 and the switching compensator 4023 are specifically shown. Position detectors 4130A and 4130 of the position detector 4021
B and 4130C are the position detecting elements 4107a and 4107a and 4130a of FIG.
Voltages are supplied in parallel via resistors 4131, which correspond to 107 b and 4107 c. Position detection element 4130A
The output terminal of the field unit 4010 (the permanent magnet 410 of FIG.
(Corresponding to 2) detection signal e1, which is a differential signal corresponding to the detection magnetic field
e2 is output and supplied to the bases of the differential transistors 4151 and 4152 of the switching generator 4022. Differential detection signals f1 and f2 corresponding to the detection magnetic field of the field magnet portion 4010 are output to the output terminal of the position detection element 4130B and are supplied to the bases of the differential transistors 4157 and 4158. At the output terminal of the position detection element 4130C, a differential detection signal g corresponding to the detection magnetic field of the field unit 4010 is detected.
1 and g2 are output, and differential transistors 4163 and 41
It is supplied to 64 bases. The detection signals e1, f1, g1 and e2, f are generated in accordance with the rotational movement of the field unit 4010.
2 and g2 change smoothly (analogically) and are electrically three-phase signals having a phase difference of 120 degrees. The detection signals e1 and e2 change to opposite phases, f1 and f2 change to opposite phases, and g1 and g2 change to opposite phases. Here, the reverse phase signal is not counted as a new phase number.

The transistor 4140 of the switching generator 22,
4141, 4142, 4143, 4144, 4145,
4146, 4147, 4148, and 4149 form a current mirror, and output (inflow) a current value proportional to the feedback current signal ib. Differential transistors 4151, 4152
Is a transistor 414 in response to the detection signals e1 and e2.
The current value of 2 is distributed to the collector side. Transistor 41
The collector current of transistor 51 is transistor 4153, 4154.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 4154 and the transistor 4141.
The inflowing current is supplied to the resistor 4171 to generate the switching signal h1 at the terminal of the resistor 4171. Transistor 4152
The collector current of the transistor 4155 is amplified twice by the current mirror of the transistors 4155 and 4156.
The current signal i1 flowing out / in from the connection end of 156 and the transistor 4143 is supplied to the switching corrector 4023. Similarly, the differential transistors 4157 and 4158 are
The current value of the transistor 4145 is distributed to the collector side in response to the detection signals f1 and f2. Transistor 4157
The collector current of the transistor 4159, 4160 is doubled by the current mirror of the transistor 4159, 4160,
The current flowing out and in from the connection end of the transistor 160 and the transistor 4144 is supplied to the resistor 4172, and the switching signal h2 is produced at the terminal of the resistor 4172.

The collector current of the transistor 4158 is doubled by the current mirror of the transistors 4161 and 4162, and the current signal i2 flowing out / in from the connection end of the transistor 4162 and the transistor 4146 is supplied to the switching corrector 4023. Similarly, the differential transistors 4163 and 4164 distribute the current value of the transistor 4148 to the collector side in response to the detection signals g1 and g2. The collector current of the transistor 4163 is doubled by the current mirror of the transistors 4165 and 4166, and the current flowing out / in from the connection end of the transistor 4166 and the transistor 4147 is converted into the resistance 417.
3 and supplies the switching signal h3 to the terminal of the resistor 4173. The collector current of the transistor 4164 is doubled by the current mirror of the transistors 4167 and 4168, so that the transistor 4168 and the transistor 41
The switching compensator 4023 is supplied with the current signal i3 flowing out / in from the connection terminal 49.

The switching signals h1, h2, h3 become three-phase voltage signals that change smoothly in response to the detection signal and are supplied to the distributor 4031. Current signals i1, i2, i3
Becomes a three-phase current signal that changes smoothly in response to the detection signal and is supplied to the switching compensator 4023 (here, switching signals h1, h2, h3 and current signals i1, i2).
i3 changes in the opposite phase, but may change in the same phase). The switching corrector 4023 includes a correction creator 4060 that creates the correction signal k1, a setting creator 4070 that creates the predetermined signal k0, and a correction comparator 4080 that compares the correction signal k1 with the predetermined signal k0. The correction generator 4060 is composed of an amplitude current device 4061 that produces an amplitude current signal jt that changes in proportion to the amplitude of the detection signal, and a correction output device 4062 that produces a correction signal k1 that is proportional to the amplitude current signal jt. Amplitude ammeter 4
061 is a current acquisition circuit 4195, 4196, 4197 to which the three-phase current signals i1, i2, i3 are input, respectively.
And diodes for current synthesis 4184, 4185, 418
6. Current acquisition circuit 4195, 4
196 and 4197 are current signals i1, i2 and i, respectively.
The current signal corresponding to the absolute value of 3 or the current signal corresponding to the unipolar value is output.

FIG. 5 shows a specific configuration of the current acquisition circuit 4195. When the switch SW is on the a side, the absolute value of the current signal i1 is created by the transistors 4200, 4201, 4202, 4203, and the transistor 420
The current signal j1 corresponding to the absolute value is output (inflow) through the 4,4205 current mirrors. When the SW is on the b side, the current signal j corresponding to the unipolar value of the current signal i1
1 is output. The configurations of the current acquisition circuits 4196 and 4197 are similar. The current acquisition circuit may be configured to obtain an output current signal corresponding to the absolute value of the input current signal, or may be configured to obtain an output current signal corresponding to the unipolar value of the input current signal. Good. An output current signal corresponding to a unipolar value is an output current signal having a value corresponding to, for example, only a positive polarity component or only a negative polarity component of a signal having positive and negative polarity components. . Current acquisition circuits 4195, 41 of the amplitude current meter 4061
96, 4197 output current signal is diode 418
4,4185,4186 to obtain the amplitude current signal jt. The amplitude current signal jt is a three-phase current signal i
1, i2, i3 are the current values of the added value of the absolute values or the added value of the unipolar values, the detection signals e1, f1, g1
Changes in proportion to the amplitude of. The correction output device 62 supplies the amplitude current signal jt to the resistor 4183 to generate the correction signal k1 at the terminal of the resistor 4183. Therefore, the amplitude current signal jt and the correction signal k1 change in proportion to the amplitude of the detection signal.

The setting generator 4070 supplies the current value of the current source 4180 to the resistor 4181 to generate a predetermined signal k0 at the terminal of the resistor 4181. The correction comparator 4080 outputs the correction signal k1 and the predetermined signal k0 to the transistors 4187, 41.
88, 4189, and 4190 are compared, and the difference current corresponding to the difference between the two is input to the current amplification circuit 4191. The current amplifier 4191 is a feedback current signal i obtained by amplifying the input current.
b is output. In this way, the detection signals e1, f1,
A correction signal k1 that responds to the amplitudes of the three-phase current signals i1, i2, i3 proportional to g1 is created, and a feedback current signal ib that responds to the comparison result of the correction signal k1 and the predetermined signal k0 is created.
Transistors 4140-4 in response to the feedback current signal ib
The output current of the current mirror 149 is changed to change the three-phase current signals i1, i2, i3 and the three-phase switching signal h1,
The amplitudes of h2 and h3 are changed. As a result, a feedback loop is configured to correct the amplitude of the three-phase switching signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the predetermined signal. Accordingly, the detection signal e of the position detector 4021
1, f1, g1 regardless of the amplitude of the current signals i1, i
2, i3 and the switching signals h1, h2, h3 have predetermined amplitudes corresponding to the predetermined signal k0. The capacitor 4192 compensates the phase of the feedback loop.

The distribution unit 4013 of FIG. 1 is composed of a distributor 4031, and the distribution signal of three phases responds to the multiplication result of the switching signal of three phases of the switching generator 4022 and the output signal of the command current unit 4050 of the command unit 4015. To produce. FIG. 6 shows a specific configuration of the distributor 4031. The output current signal d of the command current unit 4050 of the command unit 4015 is the transistor 42.
10, 4211, 4212, 4213, 4214, 42
It is supplied to the current mirrors 15 and 4216 and outputs (inflows) a current signal proportional to the output current signal d. By the transistors 4221 and 4222 and the resistors 4223 and 4224, the switching signal h1 of the switching generator 4022 and the command unit 40
The output current signal d of 15 is multiplied and the transistor 42
The output current of the transistor 4226 and the output current of the transistor 4212 is generated by inverting and outputting the multiplication current by the current mirrors of 25 and 4226, and the difference current is supplied to the resistor 4251 to distribute to the terminals of the resistor 4251. I have got m1. Therefore, the distribution signal m1 is the switching signal h.
It becomes a signal proportional to the multiplication result of 1 and the output current signal d.

Similarly, transistors 4231 and 4232 are provided.
And the resistors 4233 and 4234 are used to switch the generator 4022.
Of the output current signal d of the command unit 4015 is multiplied, and the multiplication current is inverted and output by the current mirror of the transistors 4235 and 4236.
A difference current between the output current of 36 and the output current of the transistor 4214 is made, and this difference current is applied to the resistor 4252,
The distribution signal m2 is obtained at the terminal of the resistor 4252. Therefore, the distribution signal m2 becomes a signal proportional to the multiplication result of the switching signal h2 and the output current signal d. Similarly, transistor 4
241, 4242 and resistors 4243, 4244 perform multiplication of the switching signal h3 of the switching generator 4022 and the output current signal d of the command unit 4015, and the transistors 4245, 4
Inverting the multiplication current by the current mirror of 246,
Output current of transistor 4246 and transistor 421
The difference current with the output current of 6 is made, and this difference current is
By energizing 53, the distribution signal m3 is obtained at the terminal of the resistor 4253. Therefore, the distribution signal m3 becomes a signal proportional to the multiplication result of the switching signal h3 and the output current signal d.

The driving unit 4014 of FIG. 1 is a first driving unit 404.
1 and the second driver 4042 and the third driver 4043, the three-phase coils 4011A, 4011B, the drive signals Va, Vb, Vc of the voltage waveform obtained by power amplification of the distribution signals m1, m2, m3 of the distribution unit 4013. It is supplied to the terminal of 4011C. The first driver 4041 of the driving unit 4014 is shown in FIG.
Specific configurations of the second driver 4042 and the third driver 4043 are shown. The distribution signal m1 is input to the non-inverting terminal side of the amplifier 4260 of the first driver 4041, and the resistors 4261 and 4
Amplify the voltage determined by 262 to generate the drive signal Va,
It is supplied to the power supply terminal of the coil 4011A. Similarly, the distribution signal m2 is input to the non-inverting terminal side of the amplifier 4263 of the second driver 4042, amplified by the voltage determined by the resistors 4264 and 4265 to generate the driving signal Vb, and the coil 4011.
Supply to the power supply terminal of B. Similarly, the distribution signal m3 is the third
The drive signal Vc is input to the non-inverting terminal side of the amplifier 4266 of the driver 4043, amplified by the voltage determined by the resistors 4267 and 4268, and supplied to the power supply terminal of the coil 4011C. Note that the amplifiers 4260, 4263, 4266
Is supplied with a power supply voltage of + Vm and -Vm (+ Vm
m = 15V, -Vm = -15V). Drive signals Va, V
b, Vc three-phase coils 4011A, 4011B, 4
011C is supplied with a three-phase drive current, and
A driving force in a predetermined direction is generated by an electromagnetic action with 0.

FIG. 8 shows a signal waveform for explaining the operation of this embodiment. Position detection elements 4130A, 4130B, 4130 that detect the magnetic field of the field unit 4010 as the field unit 4010 rotates (or moves relative to the three-phase coil).
C is a sinusoidal detection signal e1-e2, f1-f2, g1
-G2 is obtained [see FIG. 8 (a): the horizontal axis is the rotational position]. The switching generator 4022 and the switching corrector 4023 are three-phase current signals i1, i2, which change smoothly in response to the detection signal.
i3 [FIGS. 8B, 8C, and 8D] and three-phase switching signals h1, h2, and h3 are generated, and three-phase current signals i1, i
The correction signal k1 [FIG. 8 (e): the vertical side is the negative side is the upward direction] corresponding to the added value of the absolute values of 2 and i3 (or the added value of the unipolar values) is obtained, and the correction signal k1 is the predetermined signal k0. The feedback loop is operated so as to match with. Along with this, the amplitudes of the switching signals h1, h2, h3 are also corrected in response to the comparison result of the correction signal k1 and the predetermined signal k0 [FIG.
(F)]. The distributor 4031 has switching signals h1, h2, h
3 and three-phase distribution signals m1, m2, m3 in response to the multiplication result of the output current signal d of the command unit 4015 [FIG.
(G)]. First driver 4041 of drive unit 4014, second
The driver 4042 and the third driver 4043 drive signals Va and V obtained by power-amplifying the distribution signals m1, m2 and m3, respectively.
b, Vc are three-phase coils 4011A, 4011B, 401
Supply to 1C.

With the configuration of this embodiment, a correction signal that changes in proportion to the amplitude of the detection signal is created, and the amplitude of the switching signal can be easily corrected in response to this correction signal. As a result, even if the amplitude of the detection signal of the position detector 4021 is large or small, the amplitudes of the switching signals h1, h2, h3 are determined by the operations of the switching generator 4022 and the switching compensator 4023. It becomes a predetermined size corresponding to. Therefore, the switching signals h1, h2, h
3 and the distribution signals m1, m2, m3 and the drive signals Va, V in response to the multiplication result of the output current signal d of the command unit 4015.
b and Vc are not affected by the amplitude of the detection signal. That is, the position detecting element 4130A of the position detector 4021,
4130B and 4130C sensitivity variations and field part 401
It is not affected by the magnetic field variation of 0 or the circuit gain variation of the switching generator 22 (the influence is extremely small). Therefore, when speed control or torque control is performed using the brushless motor of the present embodiment, variations in speed control gain and torque control gain between motors are eliminated, and motor control performance during mass production becomes extremely stable. In particular, the control instability phenomenon due to the gain variation of the motor does not occur.

Further, the switching generator 4022 and the switching corrector 4
In 023, if a correction signal corresponding to the added value of the unipolar values of the three-phase current signals (for example, the value added with only the positive polarity value or the added value with only the negative polarity value) or the added value of the absolute values is generated. For example, a correction signal that changes in proportion to the amplitude of the detection signal can always be obtained with a simple circuit configuration, and accurate correction becomes possible. Of course, it goes without saying that the circuit configuration for obtaining the correction signal corresponding to the added value of the unipolar values can be simpler than the circuit configuration for obtaining the correction signal corresponding to the added value of the absolute values. In the present embodiment, even if the detection signal of the position detector changes in a smooth sine wave shape, the distribution signal and the drive signal are distorted into a trapezoidal wave shape. Acceptable for many applications,
It is preferable to eliminate distortion in order to achieve higher performance. Next, an example in which this point is improved will be described.

Embodiment 2 FIGS. 9 to 12 show the structure of a brushless motor according to Embodiment 2 of the present invention. FIG. 9 shows an overall configuration diagram. Example 2
In FIG. 9, the command unit 4015 of FIG. 9 is composed of a command current unit 4301, a multiplication command unit 4302, and a command output unit 4303 to generate a sine-wave distribution signal or drive signal that changes smoothly. The same parts as those in Example 1 described above are designated by the same reference numerals. FIG. 10 shows a specific configuration of the command current unit 4301 of the command unit 4015. Transistor 4
In response to the command signal R, 321, 4322 and resistors 4323, 4324 divert the current value of the constant current source 4320 to the collector side of the transistors 4321, 4322, and the collector currents are compared by the current mirrors of the transistors 4325, 4326. The differential current is transistor 432
Two command current signals p1 and p2 are output via the 7, 4328 and 4329 current mirrors. Therefore,
The command current device 4301 produces two command current signals p1 and p2 (p1 and p2 are proportional) in response to the command signal R,
The first command current signal p1 is supplied to the command output device 4303, and the second command current signal p2 is supplied to the multiplication command device 4302.

FIG. 11 shows the multiplication command unit 43 of the command unit 4015.
02 shows a specific configuration. Transistors 4342, 4
343 responds to the detection signals e1 and e2 of the position detection element to distribute the current value of the constant current source 4341 to the collector side, obtain the difference current by the current mirror of the transistors 4344 and 4345, and the transistors 4346, 4347 and 43
48, 4349, 4350, 4351 and the resistor 4411 obtain the voltage signal s1 in response to the absolute value of the difference current.
That is, the voltage signal s1 that responds to the absolute value of the detection signals e1-e2 is created. Similarly, a voltage signal s2 that responds to the absolute value of the detection signals f1-f2 is generated in the resistor 4412, and the voltage signal s that responds to the absolute value of the detection signals g1-g2.
3 is created in the resistor 4413. Transistor 4414,
4415, 4416, 4417 are voltage signals s1, s
2, s3 and a predetermined voltage value (including 0 V) of the constant voltage source 4418 are compared, and the command current unit 430 is operated in response to the difference voltage.
The command current signal p2 of 1 is shunted to each collector side. The collector currents of the transistors 4414, 4415, 4416 are combined to create a combined current, and the transistor 442
The combined current and the collector current of the transistor 4417 are compared by the current mirrors 1 and 4422, and the difference current is output as the multiplication command current signal q via the current mirrors of the transistors 4423 and 4424 (inflow current).

The multiplication command current signal q is responsive to the multiplication result of the voltage signals s1, s2, s3 responsive to the detection signal and the command current signal p2 responsive to the command signal. Particularly, due to the configuration of the transistors 4414, 4415, 4416, 4417, the multiplication command current signal q changes in response to the multiplication result of the command current signal p2 and the minimum value of the voltage signals s1, s2, s3. Voltage signals s1 and s that respond to the absolute value of the detection signal
The minimum value of 2, s3 is a harmonic signal that is synchronized with the detection signal and changes six times with respect to a change of one cycle of the detection signal. Therefore, the multiplication command current signal q is a harmonic signal having an amplitude proportional to the command current signal p2 and changing 6 times per cycle of the detection signal.

FIG. 12 shows the command output unit 43 of the command unit 4015.
03 shows a specific configuration. The multiplication command current signal q of the multiplication command device 4302 is input to the current mirrors of the transistors 4431 and 4432, and the current value thereof is reduced to about 1/2, and then the first command current signal p of the command current device 4301.
1 is added and combined, and the combined command current signal is output as an output current signal d through the current mirrors of the transistors 4433 and 4434 and the current mirrors of the transistors 4435 and 4436. As a result, the output current signal d of the command unit 4015 responds to the command signal and includes a harmonic signal component in a predetermined ratio. Position part 4012 of FIG.
(Position detector 4021, switching generator 4022, switching corrector 4023), distributor 4013 (distributor 4031), driver 4014 (first driver 4041 and second driver 404).
The specific configurations and operations of the second and third drivers 4043) are the same as those shown in FIGS.

FIG. 13 shows a signal waveform for explaining the operation of this embodiment. Position detection elements 4130A, 4130B, 413 that detect the magnetic field of the field unit 4010 as the field unit 4010 rotates (or moves relative to the three-phase coil).
0C is a sinusoidal detection signal e1-e2, f1-f2, g
1-g2 is obtained [see FIG. 13 (a): the horizontal axis is the rotational position]. For the command signal R having a predetermined value [FIG. 13 (b): the vertical axis is the negative side is upward], the command current unit 43 of the command unit 4015 is used.
01, the multiplication command unit 4302, and the command output unit 4303 cause the output current signal d of the command unit 4015 to include a harmonic signal component in response to the detection signal in a predetermined ratio [FIG. 13 (c)]. Switching creator 4022 and switching compensator 4
023 is a three-phase current signal i1, i2, i3 that smoothly changes in response to the detection signal of the position detector 4021 [FIG.
3 (d)] and three-phase switching signals h1, h2, h3 are generated, and the correction signal k1 corresponding to the added value of the absolute values or the added value of the unipolar values of the three-phase current signals i1, i2, i3 [Fig. 13 (e): the vertical axis is the negative side is the upward direction], and the correction signal k
The feedback loop is operated so that 1 matches the predetermined signal k0. Along with this, the correction signal k1 and the predetermined signal k0
The amplitudes of the switching signals h1, h2, h3 are also corrected in response to the comparison result of [Fig. 13 (f)]. As a result, the switching signal h
The amplitudes of 1, h2 and h3 have a magnitude in response to the predetermined signal k0 and are not affected by the amplitude of the detection signal. The distributor 4031 is provided with the switching signals h1, h2, h3 and the command unit 401.
Three-phase distribution signals m1, m2, m3 are produced in response to the result of multiplication of the output current signal d of 5 [FIG. 13 (g)]. The first driver 4041 and the second driver 404 of the driving unit 4014
The second and third drivers 4043 are distributed signals m1 and m, respectively.
The drive signals Va, Vb, and Vc obtained by power amplification of 2 and m3 are set to 3
The phase coils 4011A, 4011B, and 4011C are supplied.

With the configuration of this embodiment, the switching signals h1, h2, h3, the distribution signals m1, m2, m3, and the drive signals Va, Vb, Vc are the position detecting elements 4130A, 4130B of the position detector 4021. , 4130C sensitivity variation, field variation 4010 magnetic field variation, and switching generator 4
022 is no longer affected by the circuit gain variation of 022 (the effect is extremely small). Further, the command section produces an output signal that is proportional to the command signal and that includes a harmonic signal component that responds to the harmonic signal of the detection signal in a predetermined ratio. If a distribution signal is produced in response to the multiplication result of the output signal of the command unit and the switching signal, the distribution signals m1, m2, m3
The drive signals Va, Vb, and Vc can be three-phase sinusoidal signals that smoothly change in response to the detection signal. Therefore, the distortion of the distribution signal and the drive signal is significantly reduced, a uniform generated torque is obtained, and the motor can be smoothly driven. Further, the command unit creates two command current signals in response to the command signal by the command current device, and creates a multiplication command current signal by multiplying one command current signal by the multiplication command device by the harmonic signal of the detection signal, The output current signal obtained by synthesizing the other command current signal and the multiplication command current signal is obtained by the output device. As a result, the transistors 4414, 4415, 4416 can perform a non-linear differential operation in the multiplication command device, so that even if amplitude fluctuations of the detection signal occur, the amplitude fluctuations of the multiplication command current signal q can be reduced and the output current signal d of the command unit can be reduced. It is possible to reduce variations in the ratio of included harmonic signal components. In other words, the structure is strong against variations in sensitivity of the position detection element and variations in the magnetic field of the field unit.

Embodiment 3 FIGS. 14 to 21 show the structure of a brushless motor according to Embodiment 3 of the present invention. In the third embodiment, the mounting positional relationship between the coil and the position detecting element is shifted by an electrical angle of about 30 degrees, and the position detecting element is arranged between the coils.
It is easy to make a small motor. A drive signal shifted by 30 degrees from the detection signal of the position detection element is applied to the coil in accordance with the phase relationship between the position detection element and the coil. FIG. 14 shows an overall configuration diagram. The field unit 4510 of FIG. 14 is attached to the rotor or the moving body,
A plurality of field magnetic poles are formed by the magnetic flux generated by the permanent magnet magnetic poles to generate the field magnetic flux. Three-phase coil 4511
A, 4511B, and 4511C are attached to the stator or the fixed body, and are electrically displaced by a predetermined angle (corresponding to 120 degrees) with respect to the linkage with the magnetic flux generated by the field magnet portion 4510.

FIG. 15 shows the field part 4510 and the three-phase coil 45.
11A, 4511B and 4511C are shown. An annular permanent magnet 4602 attached to the inside of the rotor 4601 has four poles on its inner surface.
Field portion 4510 is formed. An armature iron core 4603 is arranged at a stator position facing the magnetic poles of the permanent magnet 4602, and the armature iron core 4603 has three salient pole portions 4604.
a, 4604b, 4604c are provided at a mechanical angle of 120 degrees, and three-phase coils 4605a, 4605b, 46 are provided.
05c (three-phase coils 4511A, 4511B,
4511C corresponds to each salient pole portion 4604a, 4604.
b and 4604c, respectively. Coil 46
05a, 4605b and 4605c are permanent magnets 4602.
There is an electrical phase difference of 120 degrees with respect to the interlinkage magnetic flux. The stator has three position detecting elements 460.
7a, 4607b, 4607c are arranged, and the permanent magnet 4
By detecting the magnetic pole of 602, three-phase detection signals corresponding to the relative positions of the field magnet portion and the coil are obtained. In this embodiment, the phase of the coil and the position detecting element is 1 in terms of electrical angle.
It is offset by 20 degrees. Thereby, each position detecting element can be arranged between each salient pole portion of the armature core so as to detect the magnetic field of the inner surface portion of the permanent magnet, and the motor structure can be made compact.

The command unit 4515 shown in FIG.
551, the multiplication command unit 4552, and the command output unit 4553, and produces an output current signal containing a harmonic signal component in response to the harmonic component of the detection signal at a predetermined ratio. FIG. 19 shows a specific configuration of the command current unit 4551 of the command unit 4515. Transistors 4821, 4822,
The resistors 4823 and 4824 respond to the command signal R to change the current value of the constant current source 4820 to the transistors 4821 and 4822.
Is shunted to the collector side of the transistors 4825 and 482.
The collector current is compared by the current mirror of 6,
The difference current is the transistor 4827, 4828, 482.
Two command current signals P1, through the current mirror 9
It is output as P2. Therefore, the command current generator 4551 responds to the command signal R by generating two command current signals P1 and P2.
(P1 and P2 are proportional), the first command current signal P1 is supplied to the command output device 4553, and the second command current signal P2 is supplied to the multiplication command device 4552.

FIG. 20 shows the multiplication command unit 45 of the command unit 4515.
A specific configuration of 52 is shown. Transistors 4842, 4
843 responds to the detection signals E1 and E2 of the position detection element to distribute the current value of the constant current source 4841 to the collector side, obtain the difference current by the current mirror of the transistors 4844 and 4845, and obtain the transistors 4846, 4847 and 48.
The voltage signal S1 corresponding to the absolute value of the difference current is obtained by 48, 4849, 4850, 4851 and the resistor 4911.
That is, the voltage signal S1 that responds to the absolute value of the detection signals E1-E2 is generated. Similarly, the voltage signal S2 that responds to the absolute value of the detection signals F1-F2 is generated in the resistor 4912, and the voltage signal S that responds to the absolute value of the detection signals G1-G2.
3 is created in the resistor 4913. Transistor 4914,
4915, 4916 and 4917 are voltage signals S1 and S
2, S3 is compared with a predetermined voltage value of the constant voltage source 4918, and in response to the difference voltage, the command current signal P2 of the command current generator 4551 is shunted to each collector side.

Transistors 4914, 4915, 491
The collector current of 6 is combined to produce a combined current, the combined current is compared with the collector current of the transistor 4917 by the current mirror of the transistors 4921 and 4922, and the difference current is input to the current mirror of the transistors 4923 and 4924, and the current is The value is reduced to about 1/2 and output as the multiplication command current signal Q (inflow current). The multiplication command current signal Q is responsive to the multiplication result of the voltage signals S1, S2, S3 responsive to the detection signal and the command current signal P2 responsive to the command signal R. In particular, due to the configuration of the transistors 4914, 4915, 4916, 4917, the multiplication command current signal Q changes in response to the multiplication result of the command current signal P2 and the minimum value of the voltage signals S1, S2, S3. Voltage signals S1 and S that respond to the absolute value of the detection signal
The minimum value of 2 and S3 is a harmonic signal which is synchronized with the detection signal and changes six times with respect to a change of one cycle of the detection signal. Therefore, the multiplication command current signal Q is a harmonic signal having an amplitude proportional to the command current signal P2 and changing 6 times per cycle of the detection signal.

FIG. 21 shows the command output unit 45 of the command unit 4515.
53 shows a specific configuration of 53. The multiplication command current signal Q of the multiplication command device 4552 is input to the current mirrors of the transistors 4931 and 4932, the current direction is inverted, and then added and combined with the first command current signal P1 of the command current device 4551 to obtain the combined command current. Signal to transistor 4933,
Current mirror 4934 and transistors 4935, 4
The output current signal D is output via the current mirror 936. As a result, the output current signal D of the command unit 4515 responds to the command signal and includes a harmonic signal component in a predetermined ratio. The position unit 4512 in FIG. 14 is configured by a position detector 4521, a switching generator 4522, and a switching corrector 4523, generates a switching signal from the detection signal of the position detection element of the position detector 4521, and outputs it to the distributor 4531 of the distributor 4513. Supply.

FIG. 16 shows the specific configurations of the position detector 4521, the switching generator 4522, and the switching corrector 4523.
Position detectors 4630A and 463 of the position detector 4521
0B and 4630C are the position detection elements 4607 of FIG.
a, 4607b, 4607c, and a voltage is supplied in parallel via a resistor 4631. Position detecting element 46
Differential detection signals E1 and E2 corresponding to the detection magnetic field of the field unit 4510 (corresponding to the permanent magnet 4602 in FIG. 14) are output to the output terminal of 30A, and the differential transistors 4651 and 4652 of the switching generator 4522 are output. Supplied to the base. The field detector 45 is provided at the output terminal of the position detection element 4630B.
Differential detection signals F1 and F2 corresponding to the detection magnetic field of 10 are output and supplied to the bases of the differential transistors 4657 and 4658. Differential detection signals G1 and G2 corresponding to the detection magnetic field of the field magnet portion 4510 are output to the output terminal of the position detection element 4630C, and the differential transistor 466 is output.
Supplied to 3,4664 bases. Field part 451
With the rotational movement of 0, the detection signals E1, F1, G1 and E2, F2, G2 change smoothly (analogically),
It is a three-phase signal having an electrical phase difference of 120 degrees. The detection signals E1 and E2 change in opposite phases, F1 and F2 change in opposite phases, and G1 and G2 change in opposite phases.

Transistor 464 of switch generator 4522
0,4641,4642,4643,4644,464
5, 4646, 4647, 4648 and 4649 form a current mirror, and a current value proportional to the feedback current signal Ib flows in. The differential transistors 4651 and 4652 are
The current value of the transistor 4642 is distributed to the collector side in response to the detection signals E1 and E2. Transistor 4651
The collector current of the transistor 453 is amplified twice by the current mirror of the transistors 4653 and 4654.
A current flowing out / in from the connection end of the transistor 654 and the transistor 4641 is supplied to the resistor 4671, and the switching signal H1 is generated at the terminal of the resistor 4671. The collector current of the transistor 4652 is doubled by the current mirror of the transistors 4655 and 4656, and the transistor 465
The current signal I1 flowing out / in from the connection end of 6 and the transistor 4643 is supplied to the switching corrector 4523. Similarly, the differential transistors 4657 and 4658 distribute the current value of the transistor 4645 to the collector side in response to the detection signals F1 and F2. The collector current of the transistor 4657 is doubled by the current mirror of the transistors 4659 and 4660,
The current flowing out / in from the connection end of the transistor 4644 is supplied to the resistor 4672, and the switching signal H2 is generated at the terminal of the resistor 4672.

The collector current of the transistor 4658 is doubled by the current mirror of the transistors 4661 and 4662, and the current signal 12 flowing out / in from the connection end of the transistor 4662 and the transistor 4646 is supplied to the switching corrector 4523. Similarly, the differential transistors 4663 and 4664 distribute the current value of the transistor 4648 to the collector side in response to the detection signals G1 and G2. The collector current of the transistor 4663 is doubled by the current mirror of the transistors 4665 and 4666, and the current flowing out / in from the connection end of the transistor 4666 and the transistor 4647 is converted into the resistance 467.
3 and supplies a switching signal H3 to the terminal of the resistor 4673. The collector current of the transistor 4664 is doubled by the current mirror of the transistors 4667 and 4668, and the collector current of the transistors 4668 and 4668 is amplified.
The current signal 13 flowing out / in from the connection terminal 49 is supplied to the switching corrector 4523.

The switching signals H1, H2, H3 become three-phase voltage signals that change smoothly in response to the detection signal and are supplied to the distributor 4531. Current signals I1, I2, I3
Becomes a three-phase current signal that changes smoothly in response to the detection signal and is supplied to the switching compensator 4523 (here, switching signals H1, H2, H3 and current signals I1, I2).
I3 changes in the opposite phase, but may change in the same phase). The switching corrector 4523 includes a correction creator 4560 that creates the correction signal K1, a setting creator 4570 that creates the predetermined signal K0, and a correction comparator 4580 that compares the correction signal K1 and the predetermined signal K0. The correction generator 4560 includes an amplitude current generator 4561 that produces an amplitude current signal Jt that changes in proportion to the amplitude of the detection signal and a correction output device 4562 that produces a correction signal K1 that is proportional to the amplitude current signal Jt. Amplitude current device 45
Reference numeral 61 is a current acquisition circuit 4695, 4696, 4697 to which the three-phase current signals I1, I2, I3 are input, respectively, and a diode 4684, 4685, 4686 for current combination.
It is constituted by. Current acquisition circuit 4695, 46
96 and 4697 are current signals I1, I2 and I3, respectively.
The current signal corresponding to the absolute value of or the current signal corresponding to the unipolar value is output. The specific configuration of the current acquisition circuit is the same as that shown in FIG. 5, and detailed description thereof will be omitted.

Current acquisition circuit 469 of amplitude current generator 4561
The output current signals of 5,4696 and 4697 are combined through the diodes 4684, 4685 and 4686 to obtain the amplitude current signal Jt. Since the amplitude current signal Jt is a current signal of the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values, the detection signals E1, F
1, it changes in proportion to the amplitude of G1. Correction output device 456
2 supplies the amplitude current signal Jt to the resistor 4683 and produces the correction signal K1 at the terminal of the resistor 4683. Therefore, the amplitude current signal Jt and the correction signal K1 change in proportion to the amplitude of the detection signal. The setting generator 4570 uses the current source 46
A current value of 80 is applied to the resistor 4681 to generate a predetermined signal K0 at the terminal of the resistor 4681. Correction comparator 4580
Applies the correction signal K1 and the predetermined signal K0 to the transistor 468.
7, 4688, 4689, and 4690 are compared, and the difference current corresponding to the difference between the two is input to the current amplification circuit 4691. The current amplifier 4691 outputs the feedback current signal Ib obtained by amplifying the input current.

In this way, the detection signals E1, F1, G
A correction signal K1 that responds to the amplitudes of the three-phase current signals I1, I2, and I3 that are proportional to 1 is created, and a feedback current signal Ib that responds to the comparison result of the correction signal K1 and the predetermined signal K0 is created. In response, transistors 4640-46
By changing the output current of the current mirror 49, the three-phase current signals I1, I2, I3 and the three-phase switching signals H1, H
2, H3 is changing. As a result, a feedback loop for correcting the magnitudes of the three-phase current signal and the correction signal in response to the result of comparison between the correction signal and the predetermined signal is formed. As a result, the amplitudes of the current signals I1, I2, I3 and the switching signals H1, H2, H3 have a predetermined magnitude corresponding to the predetermined signal K0 regardless of the amplitudes of the detection signals E1, F1, G1 of the position detector 4521. Become. The capacitor 4692 compensates the phase of the feedback loop. The distributor 4513 in FIG. 14 is composed of a distributor 4531 and produces a three-phase distribution signal in response to the multiplication result of the switching signal of the switching generator 4522 and the output signal of the command unit 4515.

FIG. 17 shows a concrete structure of the distributor 4531. The output current signal D of the command output device 4531 of the command unit 4515 is output from the transistors 4710, 4711, 4712,
The output current signal D is supplied to the current mirror 4713.
Outputs a current signal proportional to. Transistor 472
1, 4722 and resistors 4723, 4724 multiplies the switching signal H1 of the switching generator 4522 and the output current signal D of the command unit 4515 to generate the transistors 4721 and 472.
The H1 · D multiplication signal is output in the opposite phase to the 2 collector side. Similarly, transistors 4731 and 4732 and a resistor 4
733 and 4734 multiply the switching signal H2 of the switching generator 4522 and the output current signal D of the command unit 4515, and set the collector side of the transistors 4731 and 4732 to H level.
The 2 · D multiplication signal is output in the opposite phase. Similarly, by the transistors 4741 and 4742 and the resistors 4743 and 4744, the switching signal H3 of the switching generator 4522 and the command unit 451.
5 is multiplied by the output current signal D to obtain the transistor 474.
The H3 · D multiplication signal is output in anti-phase to the collector side of 1 and 4742. The collector current of the transistor 4721 and the collector current of the transistor 4742 are combined to generate a combined current obtained by subtracting and combining the multiplication signals H1 · D and H3 · D for the two phases, and the transistors 4725, 4726, 472.
Inverted output is made via the current mirror of No. 7. Similarly, the collector current of transistor 4731 and transistor 4731
22 collector currents are combined to generate a multiplication signal H2 for two phases.
-D, H1 and D are subtracted and combined to generate a combined current, which is inverted and output via the current mirror of transistors 4735, 4736, and 4737. Similarly, the transistor 47
The collector current of 41 and the collector current of the transistor 4732 are combined to generate multiplication signals H3 · D and H2 · D for two phases.
And the transistor 47
Inverted output is made via the current mirrors 45, 4746, 4747.

Transistors 4726, 4736 and 474
The output currents of 6 are combined to form transistors 4714, 4
The current is supplied to the current mirror composed of 715, 4716, and 4717, and the combined current is reduced to about 1/3 to obtain the current. Output current of transistor 4727 and transistor 4
A differential current with respect to the output current of 715 is made, this differential current is passed through the resistor 4751, and the distribution signal M is applied to the terminal of the resistor 4751.
I have one. Similarly, a difference current between the output current of the transistor 4737 and the output current of the transistor 4716 is created, and this difference current is applied to the resistor 4752 to generate the resistance 475.
The distributed signal M2 is obtained at the second terminal. Similarly, a difference current between the output current of the transistor 4747 and the output current of the transistor 4717 is created, and this difference current is supplied to the resistor 4753 to obtain the distribution signal M3 at the terminal of the resistor 4753. In this way, by obtaining the multiplication current signal of the switching signal and the output signal of the command unit and creating the distribution signal by combining the multiplication current signals of at least two phases, the distribution signal with respect to the detection signal of the position detector is generated. The phase of is shifted by about 30 degrees.

The driving unit 4514 of FIG. 14 is the first driving unit 45.
41, the second driver 4542 and the third driver 4543, and the distribution signal M of the distributor 4531 of the distributor 4513.
Drive signals Va, Vb, V obtained by power-amplifying 1, M2, M3
c is supplied to the terminals of the three-phase coils 4511A, 4511B, 4511C. FIG. 18 shows a specific configuration of the first driver 4541, the second driver 4542, and the third driver 4543 of the driving unit 4514. The distribution signal M1 is transmitted to the first driver 454.
1 is input to the non-inverting terminal side of the amplifier 4760, and the resistor 4
The drive signal Va is generated by amplifying the voltage determined by 761 and 4762, and is supplied to the power supply terminal of the coil 4511A. Similarly, the distribution signal M2 is transmitted to the amplifier 47 of the second driver 4542.
Input to the non-inverting terminal side of 63, resistors 4764, 476
The voltage determined by 5 is amplified to generate the drive signal Vb, which is supplied to the power supply terminal of the coil 4511B. Similarly, the distribution signal M3 is input to the non-inverting terminal side of the amplifier 4766 of the third driver 4543, amplifies the voltage determined by the resistors 4767 and 4768 to generate the driving signal Vc, and supplies the driving signal Vc to the power feeding terminal of the coil 4511C. Note that the amplifiers 4760 and 476 are
The power supply voltages of + Vm and -Vm are supplied to 3,4766 (+ Vm = 15V, -Vm = -15V).

Three-phase coils 4511A, 4511B, and 4511C are supplied with three-phase drive currents by the drive signals Va, Vb, and Vc, and a driving force in a predetermined direction is generated by electromagnetic action with the field magnet portion 4510. FIG. 22 shows a signal waveform for explaining the operation of this embodiment. Position detecting elements 4630A and 4630A, 4630A that detect the magnetic field of the field unit 4510 as the field unit 4510 rotates (or moves relative to the three-phase coil).
630B and 4630C are sinusoidal detection signals E1-E.
2, F1-F2, G1-G2 are obtained [see FIG. 26 (a): the horizontal axis is the rotational position]. Command signal R of predetermined value [Fig. 26
(B): the vertical axis is the negative side is the upper side]
By the operation of the command current generator 4551, the multiplication command device 4552, and the command output device 4553 of FIG. 5, the output current signal D of the command unit 4515 becomes to include the harmonic signal component corresponding to the detection signal in a predetermined ratio [Fig. c)].

Switching creator 4522 and switching corrector 4523
Is a three-phase current signal I1, I2, I3 that smoothly changes in response to the detection signal of the position detector 4521 [see FIG.
(D)] and three-phase switching signals H1, H2, H3 are generated, and the correction signal K1 corresponding to the added value of the absolute values or the added value of the unipolar values of the three-phase current signals I1, I2, I3 [FIG. (E): the vertical axis is the negative side is the upward direction], and the correction signal K
The feedback loop is operated so that 1 matches the predetermined signal K0. Accordingly, the correction signal K1 and the predetermined signal K0
The amplitudes of the switching signals H1, H2, and H3 are also corrected in response to the comparison result of [Fig. 26 (f)]. As a result, the switching signal H
The amplitudes of 1, H2 and H3 have a magnitude in response to the predetermined signal K0 and are not affected by the amplitude of the detection signal. The distributor 4531 uses the switching signals H1, H2, H3 and the command unit 451.
Three-phase distribution signals M1, M2, M3 are produced in response to the multiplication result of the output current signal D of No. 5. In particular, the distribution signals M1, M2, M3 are detected signals E1-E2, F1- by combining at least two phases of the multiplication result to create a distribution signal.
The phase is shifted by about 30 degrees with respect to F2, G1-G2 [FIG. 26 (g)]. First driver 45 of driver 4514
41, the second driver 4542, and the third driver 4543 use three-phase coils 4511A and 4511 to generate drive signals Va, Vb, and Vc obtained by power-amplifying the distribution signals M1, M2, and M3, respectively.
B, 4511C.

In the present embodiment, a correction signal whose magnitude changes in proportion to the amplitude of the detection signal is created, and the amplitude of the switching signal is corrected in response to the result of comparison between the correction signal and the predetermined signal. As a result, the switching signals H1, H2, H3 and the distribution signal M
1, M2, M3 and drive signals Va, Vb, Vc are the position detection elements 4630A, 4630B, 4 of the position detector 521.
It is not affected by the sensitivity variation of 630C, the magnetic field variation of the field magnet unit 4510, or the circuit gain variation of the switching generator 4522 (the influence is extremely small). In addition, in the switching generator 4522 and the switching corrector 4523, a correction signal corresponding to the addition value of the unipolar values or the addition value of the absolute values of the three-phase current signals is generated, and the amplitude of the switching signal is generated in response to the correction signal. Is being corrected. Therefore, the correction signal corresponding to the amplitude of the detection signal can always be obtained with a simple circuit configuration, and accurate correction can be performed.

If necessary, an output signal having a configuration such as the command unit of this embodiment and including a predetermined proportion of a harmonic signal component proportional to the command signal and responding to the harmonic signal of the detection signal is provided. It is also possible to create a distribution signal in response to the multiplication result of this output signal and the switching signal. As a result, the distribution signals M1, M2, M3 and the drive signals Va,
Vb and Vc can be three-phase sinusoidal signals that smoothly change in response to the detection signal. Therefore, the distortion of the distribution signal and the drive signal is significantly reduced, a uniform generated torque is obtained, and the motor can be smoothly driven. Further, the command unit creates two command current signals in response to the command signal by the command current device, and creates a multiplication command current signal by multiplying one command current signal by the multiplication command device by the harmonic signal of the detection signal, The output device produces an output current signal by combining the other command current signal and the multiplication command current signal. As a result, the transistor 491 in the multiplication commander
4, 4915 and 4916 can be operated in a non-linear differential operation, the amplitude variation of the multiplication command current signal can be reduced even if the amplitude variation of the detection signal occurs, and the harmonic signal components included in the output current signal D of the command unit can be reduced. It is possible to reduce the variation in the ratio. In other words, the structure is strong against variations in sensitivity of the position detection element and variations in the magnetic field of the field unit. Further, with the configuration of this embodiment, the position detecting element can be arranged with a high degree of freedom, and by disposing the position detecting element between the salient pole portions of the armature core, the motor structure can be made compact.

Fourth Embodiment FIGS. 23 to 26 show the structure of a brushless motor according to a fourth embodiment of the present invention. Also in this embodiment, the mounting positional relationship between the coil and the position detecting element is shifted by an electrical angle of about 30 degrees,
The detection element is arranged between the coils to facilitate the production of a small motor. FIG. 23 shows an overall configuration diagram. In this embodiment, the switching generator 50 outputs a switching signal that is phase-shifted by about 30 degrees in electrical angle from the detection signal of the position detecting element.
22 and the distributor 5031 of the distributor 4513 does not perform the phase shift. In addition, the command unit 4
The configuration of the command output device 5053 of 515 is such that the command current signal and the multiplication command current signal are subtractively combined. The same parts as those in Example 3 described above are designated by the same reference numerals.

The position detector 45 of the position portion 4512 is shown in FIG.
21 shows the specific configurations of the switching generator 21, the switching generator 5022, and the switching corrector 5023. Position detecting element 4 of position detector 4521
Reference numerals 630A, 4630B, and 4630C correspond to the position detection elements 4607a, 4607b, and 4607c in FIG. 15 described above, and voltages are supplied in parallel via the resistor 4631. The field detector 45 is provided at the output terminal of the position detection element 4630A.
The differential detection signals E1 and E2 corresponding to the detection magnetic field of 10 (the permanent magnet 4602 in FIG. 15) are output, and the switching generator 5
022 is supplied to the bases of the differential transistors 4153 and 4154. Differential detection signals F1 and F2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 4630B and are supplied to the bases of the differential transistors 5160 and 5161. Differential detection signals G1 and G2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 4630C and are supplied to the bases of the differential transistors 5167 and 5168. The detection signals E1, F1, G1 change smoothly with the rotational movement of the field unit 4510, and are three-phase signals having an electrical phase difference of 120 degrees.

Transistor 514 of switch creator 5022
0,5141, 5142, 5143, 4144, 514
5,5146, 5147, 5148, 5149, 515
0, 5151 and 5152 form a current mirror, and a current value proportional to the feedback current signal Ib flows in. The differential transistors 5153 and 5154 distribute the current value of the transistor 5142 to the collector side in response to the detection signals E1 and E2. The collector current of the transistor 5153 is doubled by the current mirror of the transistors 5155 and 5156, and the current flowing out / in from the connection end of the transistor 5156 and the transistor 5141 is converted to the resistance 517.
4 The collector current of the transistor 5154 is doubled by the current mirror of the transistors 5157, 5158, 5159,
The current flowing out and in from the connection end of the transistor 58 and the transistor 5143 is supplied to the resistor 5175,
The current signal I1 flowing out / in from the connection end of the transistor 5144 is supplied to the switching corrector 5023. Similarly, the differential transistors 5160 and 5161 distribute the current value of the transistor 5146 to the collector side in response to the detection signals F1 and F2. The collector current of the transistor 5160 is doubled by the current mirror of the transistors 5162 and 5163, and the current flowing out / in from the connection end of the transistor 5163 and the transistor 5145 is supplied to the resistor 5175.

The collector current of the transistor 5161 is doubled by the current mirror of the transistors 5164, 5165, 5166, and the current flowing out / in from the connection end of the transistor 5165 and the transistor 5147 is supplied to the resistor 5176, so that the transistor 5166 and the transistor 5166 are connected. The current signal 12 flowing out / in from the connection end of 5148 is supplied to the switching corrector 5023. Similarly, the differential transistors 5167 and 5168 have detection signals G1 and
In response to G2, the current value of the transistor 5150 is distributed to the collector side. The collector current of the transistor 5167 is doubled by the current mirror of the transistors 5169 and 5170, and the current flowing out / in from the connection end of the transistor 5170 and the transistor 5149 is supplied to the resistor 5176. The collector current of the transistor 5168 is the transistors 5171, 5172, 5173.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 5172 and the transistor 5151.
The inflowing current is supplied to the resistor 5174, and the transistor 5
The current signal 13 flowing out / in from the connection end of the transistor 173 and the transistor 5152 is supplied to the switching corrector 5023.

The switching signals H1, H2, H3 become three-phase voltage signals which change smoothly in response to the detection signal and are supplied to the distributor 5031. Each switching signal is a signal obtained by synthesizing at least two phases of the detection signal, and is phase-shifted by about 30 degrees with respect to the detection signal. The current signals I1, I2, I3 become three-phase current signals that change smoothly in response to the detection signal, and are supplied to the switching corrector 5023. The switching corrector 5023 includes a correction creator 5060 that creates the correction signal K1, a setting creator 5070 that creates the predetermined signal K0, and a correction comparator 5080 that compares the correction signal K1 and the predetermined signal K0. The correction generator 5060 includes an amplitude current generator 5061 and an amplitude current signal J which generate an amplitude current signal Jt proportional to the amplitude of the detection signal.
A correction output device 506 that produces a correction signal K1 proportional to t
2. Amplitude ammeter 5061 is 3
The current acquisition circuits 5195, 5196, 5197 are configured to receive the phase current signals I1, I2, I3, respectively. Current acquisition circuit 5195, 5196, 519
Reference numeral 7 outputs a current signal corresponding to the absolute value of the current signals I1, I2, I3 or a current signal corresponding to the unipolar value, respectively. The specific configuration of the current acquisition circuit is the same as that shown in FIG. 5, and detailed description thereof will be omitted.

Current acquisition circuit 519 of amplitude current device 5061
The output current signals of 5, 5196 and 5197 are combined to obtain the amplitude current signal Jt. Since the amplitude current signal Jt is a current signal of the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values, the detection signals E1, F
1, it changes in proportion to the amplitude of G1. Correction output device 506
2 supplies the amplitude current signal Jt to the resistor 5199, and produces the correction signal K1 at the terminal of the resistor 5199. Therefore, the amplitude current signal Jt and the correction signal K1 change in proportion to the amplitude of the detection signal. The setting generator 5070 uses the current source 51
A current value of 80 is applied to the resistor 5181 to generate a predetermined signal K0 at the terminal of the resistor 5681. Correction comparator 5080
Applies the correction signal K1 and the predetermined signal K0 to the transistor 518.
7, 5188, 5189, and 5190 are compared, and the difference current corresponding to the difference between the two is input to the current amplification circuit 5191. The current amplifier 5191 outputs the feedback current signal Ib obtained by amplifying the input current. In this way, the detection signal E
1, F1, G1 three-phase current signals I1, I2,
The correction signal K1 is generated in response to the amplitude of I3, and the correction signal K
1 and the feedback current signal I in response to the comparison result of the predetermined signal K0
b, and the transistor 5 in response to the feedback current signal Ib
The output currents of the current mirrors 140 to 5152 are changed to change the amplitudes of the three-phase current signals I1, I2, I3 and the three-phase switching signals H1, H2, H3. As a result, a feedback loop is configured to correct the amplitude of the three-phase switching signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the predetermined signal. As a result, the current signal I is detected regardless of the amplitudes of the detection signals E1, F1, G1 of the position detector 4521.
1, I2, I3 and the switching signals H1, H2, H3 have predetermined amplitudes corresponding to the predetermined signal K0. The capacitor 5192 compensates the phase of the feedback loop.

The distributor 4513 in FIG. 23 is a distributor 5031.
And produces a distribution signal in response to the multiplication result of the switching signal of the switching generator 5022 and the output signal of the command unit 4515. FIG. 25 shows a specific configuration of the distributor 5031. The output current signal D of the command output unit 1053 of the command unit 4515 is the transistors 5210, 5211, 5212, 5
It is supplied to the current mirrors 213, 5214, 5215 and 5216 and outputs a current signal proportional to the output current signal D. Transistors 5221 and 5222 and resistor 522
3, 5224, the switching signal H of the switching generator 5022
1 is multiplied by the output current signal D of the command unit 4515, and the multiplication signal of H1 · D is output to the collector side of the transistor 5221. The collector current of the transistor 5221 is doubled by the current mirror of the transistors 5225 and 5226, and the current flowing out / in from the connection end of the transistor 5226 and the transistor 5212 is transferred to the resistor 52.
51 to obtain the distribution signal M1 at the terminal of the resistor 5251. Therefore, the distribution signal M1 is proportional to the multiplication signal H1 · D. Similarly, the transistors 5231 and 5232 and the resistor 5
The switching signal H2 of the switching generator 5022 and the output current signal D of the command unit 4515 are multiplied by 233 and 5234, and the multiplication signal of H2 · D is output to the collector side of the transistor 5231.

The collector current of the transistor 5231 is doubled by the current mirror of the transistors 5235 and 5236, and the current flowing out / in from the connecting end of the transistor 5236 and the transistor 5214 is transferred to the resistor 52.
52, and the distribution signal M2 is obtained at the terminal of the resistor 5252. Therefore, the distribution signal M2 is proportional to the multiplication signal H2 · D. Similarly, the transistors 5241 and 5242 and the resistor 5
The switching signal H3 of the switching generator 5022 and the output current signal D of the command unit 4515 are multiplied by 243 and 5244, and the multiplication signal of H3 · D is output to the collector side of the transistor 5241. The collector current of the transistor 5241 is doubled by the current mirror of the transistors 5245 and 5246, and the current flowing out and in from the connection end of the transistor 5246 and the transistor 5216 is supplied to the resistor 5253, and the distribution signal M is supplied to the terminal of the resistor 5253.
Get 3. Therefore, the distribution signal M3 is proportional to the multiplication signal M3 · D.

The drive unit 4514 shown in FIG. 23 is the first drive unit 45.
41, the second driver 4542 and the third driver 4543, and the distribution signal M of the distributor 5031 of the distributor 4513.
Drive signals Va, Vb, V obtained by power-amplifying 1, M2, M3
c is supplied to the terminals of the three-phase coils 4511A, 4511B, 4511C. First driver 454 of driver 4514
The specific configurations and operations of the first, second driver 4542 and the third driver 4543 are the same as those shown in FIG. 18 described above, and detailed description thereof will be omitted. The command unit 451 is shown in FIG.
5 shows a specific configuration of the command output unit 5053 of No. 5. First command current signal P1 of command current device 4551 and multiplication command device 4
The combined command current signal Q of 552 is combined to create a combined command current signal, and the current mirrors of the transistors 5261 and 5262 and the current mirrors of transistors 5263 and 5264 create an output current signal D in response to the combined command current signal, and the distributor 5031. In addition,
Specific configurations and operations of the command current unit 4551 and the multiplication command unit 4552 are the same as those shown in FIGS. 19 and 20 described above, and detailed description thereof will be omitted. The configuration of this embodiment also has switching signals H1, H2, H3 and distribution signals M1, M2.
M3 and the drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. Further, the distributed signals M1, M2, M3 and the drive signals Va, Vb, Vc smoothly change in a sinusoidal shape in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly. further,
The position detecting element can be arranged freely, and the motor structure can be made compact by disposing the position detecting element between the salient pole portions of the armature core.

Embodiment 5 FIGS. 27 to 29 show the structure of a brushless motor according to Embodiment 5 of the present invention. FIG. 27 shows an overall configuration diagram of the fifth embodiment. In the present embodiment, the switching generator 5302 and the switching corrector 5
In 303, a correction signal that changes in proportion to the amplitude of the detection signal of the position detector 4521 is generated, a predetermined signal including a harmonic signal component of the detection signal is generated, and in response to the comparison result of the correction signal and the predetermined signal, Thus, the amplitude of the switching signal of the switching generator 5302 is corrected. Further, the mounting positional relationship between the coil and the position detecting element is shifted by an electrical angle of about 30 degrees, and the detecting element is arranged between the coils, so that the small motor can be easily manufactured. The same parts as those in this embodiment described above are designated by the same reference numerals.

The position detector 452 at the position 4512 is shown in FIG.
1 shows the specific configurations of 1, the switching generator 5302, and the switching corrector 5303. Position detecting element 46 of position detector 4521
30A, 4630B, and 4630C correspond to the position detection elements 4607a, 4607b, and 4607c in FIG. 15 described above, and a voltage is supplied in parallel via the resistor 4631. The field detector 45 is provided at the output terminal of the position detection element 4630A.
Differential detection signals E1 and E2 corresponding to the detection magnetic field of 10 (corresponding to the permanent magnet 4602 in FIG. 15) are output and supplied to the bases of the differential transistors 5351 and 5352 of the switching generator 5302. At the output terminal of the position detection element 4630B, differential detection signals F1 and F corresponding to the detection magnetic field are provided.
2 is output and supplied to the bases of the differential transistors 5357 and 5358. Differential detection signals G1 and G corresponding to the detection magnetic field are provided at the output terminals of the position detection element 4630C.
2 is output and supplied to the bases of the differential transistors 5363 and 5364. The detection signals E1, F1, G1 change smoothly with the rotational movement of the field unit 4510, and are three-phase signals having an electrical phase difference of 120 degrees.

Transistor 534 of switching generator 5302
0, 5341, 5342, 5343, 5344, 534
5, 5346, 5347, 5348, 5349 form a current mirror, and a current value proportional to the feedback current signal Ib flows in. The differential transistors 5351 and 5352 are
In response to the detection signals E1 and E2, the current value of the transistor 5342 is distributed to the collector side. Transistor 5351
The collector current of the transistor 5353 is amplified twice by the current mirror of the transistors 5353 and 5354.
A current flowing out / in from the connection end of the transistor 354 and the transistor 5341 is supplied to the resistor 5371, and the switching signal H1 is obtained at the terminal of the resistor 5371. The collector current of transistor 5352 is doubled by the current mirror of transistors 5355 and 5356,
The current signal 11 flowing out / in from the connection end of the transistor 6 and the transistor 5343 is supplied to the switching corrector 5303. Similarly, the differential transistors 5357 and 5358 distribute the current value of the transistor 5345 to the collector side in response to the detection signals F1 and F2.

The collector current of the transistor 5357 is doubled by the current mirror of the transistors 5359 and 5360, and the current flowing out / in from the connecting end of the transistor 5360 and the transistor 5344 is transferred to the resistor 53.
72, and the switching signal H2 is obtained at the terminal of the resistor 5372. The collector current of the transistor 5358 is 2 by the current mirror of the transistors 5361 and 5362.
Doubled, transistor 5362 and transistor 5
The current signal I2 flowing out / in from the connection end of 346 is supplied to the switching corrector 5303. Similarly, the differential transistors 5363 and 5364 distribute the current value of the transistor 5348 to the collector side in response to the detection signals G1 and G2. The collector current of the transistor 5363 is doubled by the current mirror of the transistors 5365 and 5366, so that the transistor 5366 and the transistor 53
The current flowing out / in from the connection end of 47 is supplied to the resistor 5373, and the switching signal H3 is obtained at the terminal of the resistor 5373. The collector current of the transistor 5364 is doubled by the current mirror of the transistors 5367 and 5368, and the transistor 5368 and the transistor 534 are amplified.
The current signal 13 flowing out / in from the connection terminal 9 is supplied to the switching corrector 5303.

The switching signals H1, H2, H3 become three-phase voltage signals which change smoothly in response to the detection signal and are supplied to the distributor 4531. Current signals I1, I2, I3
Becomes a three-phase current signal that changes smoothly in response to the detection signal and is supplied to the switching corrector 5303. The switching compensator 5303 is a compensation generator 53 that produces the compensation signal K1.
10 and a setting generator 5320 for generating a predetermined signal K0
And a correction comparator 5330 that compares the correction signal K1 with the predetermined signal K0. Correction creator 5310
Is an amplitude current signal J that changes in proportion to the amplitude of the detection signal.
It is composed of an amplitude current generator 5311 for generating t and a correction output device 5312 for generating a correction signal K1 proportional to the amplitude current signal Jt. The amplitude current device 5311 is composed of current acquisition circuits 5395, 5396, 5397 to which the three-phase current signals I1, I2, I3 are input, respectively. Current acquisition circuit 5395, 5396, 5397
Outputs a current signal corresponding to the absolute value of the current signals I1, I2, I3 or a current signal corresponding to the unipolar value, respectively. The specific configuration of the current acquisition circuit is the same as that shown in FIG. 5, and detailed description thereof will be omitted.

Current acquisition circuit 539 of amplitude current device 5311
The output current signals of 5,5396 and 5397 are combined to obtain the amplitude current signal Jt. Since the amplitude current signal Jt is a current signal of the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values, the detection signals E1, F
1, it changes in proportion to the amplitude of G1. Correction output device 531
2 changes the amplitude current signal Jt into the correction signal K1 by the resistor 5399 and outputs it. Therefore, the amplitude current signal Jt and the correction signal K1 change in proportion to the amplitude of the detection signal. The setting generator 5320 of FIG. 28 includes a setting current generator 5321 that outputs two setting current signals, and a multiplication setting current signal that generates a harmonic signal synchronized with the detection signal and multiplies it by one of the setting current signals. 5322, and a setting output device 5323 that outputs a predetermined signal K0 proportional to the combined set current signal obtained by combining the other set current signal and the multiplication set current signal. FIG. 29 shows a specific configuration of the setting generator 5320. Setting current device 5321
Is composed of two current sources 5481, 5482 and outputs two set current signals Pf, Pg.

Transistor 540 of multiplication setter 5322
2, 5403 distribute the current value of the constant current source 5401 to the collector side in response to the detection signals E1 and E2 of the position detecting element, obtain the difference current by the current mirror of the transistors 5404 and 5405, and obtain the transistors 5406 and 540.
7, 5408, 5409, 5410, 5411 and resistor 5
Voltage signal S1 responding to the absolute value of the difference current by 461
Get. That is, the voltage signal S1 that responds to the absolute value of the detection signals E1-E2 is generated. Similarly, the detection signal F1-
The voltage signal S2 responsive to the absolute value of F2 is produced at the terminal of the resistor 5462, and the voltage signal S3 responsive to the absolute value of the detection signals G1-G2 is produced at the terminal of the resistor 5463. Transistors 5464, 5465, 5466, 5467 and diodes 5468, 5469 provide voltage signals S1, S2,
S3 is compared with a predetermined voltage value (including 0 V) of the constant voltage source 5475, and the set current signal Pf is shunted to each collector side in response to the difference voltage. Transistors 5464,546
The collector currents of 5 and 5466 are combined to produce a combined current, and the combined current and the collector current of the transistor 5467 are compared by the current mirror of the transistors 5471 and 5472.
It is input to the current mirror 5474, and its current value is reduced to about 1/2 and output as a multiplication setting current signal Qg (inflow current).

The setting output unit 5323 is a multiplication setting unit 532.
The combined setting current signal obtained by combining the multiplication setting current signal Qg of 2 and the other setting current signal Pg of the setting current unit 5321 is applied to the resistor 5491, and the predetermined signal K is applied from the terminal of the resistor 5491.
Outputs 0. The multiplication setting current signal Qg of the multiplication setting unit 5322 is the voltage signals S1, S2, S3 responsive to the detection signal.
And the result of multiplication of the set current signal Pf of the set current device 5321. Transistors 5464, 5465, 54
With the configuration of 66, 5467, voltage signals S1, S2, S
The multiplication setting current signal Qg changes in response to the multiplication result of the minimum value of 3 and the setting current signal Pf. The minimum value of the voltage signals S1, S2, S3 that responds to the absolute value of the detection signal is a harmonic signal that is synchronized with the detection signal and that changes six times with respect to a change in one cycle of the detection signal. Therefore, the multiplication setting current signal Qg
Is a harmonic signal having an amplitude proportional to the set current signal Pf and changing 6 times per cycle of the detection signal. The predetermined signal K0 of the setting output device 5323 is the multiplication setting current signal Qg.
Since it is proportional to the combined set current signal of the set current signal Pg and the set current signal Pg, a harmonic signal component responsive to the detection signal is included in a predetermined ratio.

The correction comparator 5330 of FIG. 28 compares the correction signal K1 with the predetermined signal K0 and outputs the feedback current signal Ib of the current amplification circuit 5391 in response to the difference between the two. As a result, the correction signal K1 proportional to the amplitude of the detection signal is generated by the three-phase current signals I1, I2, I3, and the feedback current signal Ib corresponding to the comparison result of the correction signal K1 and the predetermined signal K0 is generated. The output currents of the current mirrors of the transistors 5340 to 5349 change in response to the feedback current signal Ib, and the amplitudes of the three-phase current signals I1, I2, I3 and the three-phase switching signals H1, H2, H3 change. That is, a feedback loop is configured to correct the amplitude of the three-phase switching signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the predetermined signal. As a result, the current signals I1, I2, I3 and the switching signals H1, H are irrespective of the amplitudes of the detection signals E1, E2, F1, F2, G1, G2 of the position detector 5521.
The amplitudes of 2 and H3 have a predetermined magnitude corresponding to the predetermined signal K0. The capacitor 51392 compensates the phase of the feedback loop described above. At this time, the setting creator 513
The predetermined signal K0 of 20 is a voltage signal including a predetermined ratio of a harmonic signal component that responds to the harmonic signal of the detection signal. Since the amplitudes of the switching signals H1, H2, H3 change in response to the predetermined signal K0, the switching signals H1, H2, H3 are sine wave-shaped smooth voltage signals having the amplitude corresponding to the predetermined signal K0.

Distributor 4531 of distributor 4513 in FIG.
And a first driver 4541 and a second driver 4 of the driving unit 4514.
The configurations and operations of the 542 and the third driver 4543 are the same as those shown in FIGS. 17 and 18 described above, and detailed description thereof will be omitted. The configuration of the command current unit 4050 of the command unit 4515 of FIG. 27 is similar to that shown in FIG. The output signal d of the command current unit 4050 is the distributor 45.
31 is connected to the input signal D. The operation of the command current device 4050 is the same as the above-described description of FIG. 3, and detailed description thereof will be omitted. Also in the configuration of this embodiment, the correction signal K1 that changes in proportion to the amplitude of the detection signal of the position detector is generated, and the amplitudes of the switching signals H1, H2, H3 are generated in response to the comparison result of the correction signal K1 and the predetermined signal K0. Is being corrected. as a result,
Switching signals H1, H2, H3 and distribution signals M1, M2, M3
The drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. In addition, the setting creator 5 of the switching corrector 5303
At 320, a high frequency signal responsive to the detection signal is obtained, a multiplication setting current signal is generated by multiplying the harmonic signal, and a predetermined signal K0 including a harmonic signal component responsive to the multiplication setting current signal is generated at a predetermined ratio. . In response to the comparison result of the correction signal K1 and the predetermined signal K0, the switching signals H1, H2,
By correcting the amplitude of H3, it is possible to obtain a switching signal that smoothly changes in a sinusoidal wave in response to the detection signal. Since the distribution signals M1, M2, M3 are generated in response to the multiplication result of the switching signals H1, H2, H3 and the output signal of the command unit, the distribution signals M1, M2, M3 and the driving signals Va, Vb, Vc are detected. It changes smoothly in a sinusoidal shape in response to a signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly.

Embodiment 6 FIGS. 30 to 32 show the structure of a brushless motor according to Embodiment 6 of the present invention. FIG. 30 shows an overall configuration diagram of the sixth embodiment. In this embodiment, the switching generator 5502 and the switching corrector 5
In 503, a correction signal that is proportional to the amplitude of the detection signal of the position detector 4521 and includes a harmonic signal component of the detection signal is generated, and in response to the result of comparison between the correction signal and the predetermined signal, the switching generator 5502 The amplitude of the switching signal of is corrected. Further, the mounting positional relationship between the coil and the position detecting element is shifted by an electrical angle of about 30 degrees, and the detecting element is arranged between the coils, so that the small motor can be easily manufactured. The same parts as those in this embodiment described above are designated by the same reference numerals. The position detector 45 of the position portion 4512 is shown in FIG.
21 shows a specific configuration of the switch generator 5502 and the switch corrector 5503. Position detecting element 4 of position detector 4521
Reference numerals 630A, 4630B, and 4630C correspond to the position detection elements 4607a, 4607b, and 4607c in FIG. 15 described above, and voltages are supplied in parallel via the resistor 4631. The field detector 45 is provided at the output terminal of the position detection element 4630A.
Differential detection signals E1 and E2 corresponding to the detection magnetic field of 10 (corresponding to the permanent magnet 4602 in FIG. 15) are output and supplied to the bases of the differential transistors 5551 and 5552 of the switching generator 5502. At the output terminal of the position detection element 4630B, differential detection signals F1 and F corresponding to the detection magnetic field are provided.
2 is output and supplied to the bases of the differential transistors 5557 and 5558. Differential detection signals G1 and G corresponding to the detection magnetic field are provided at the output terminals of the position detection element 4630C.
2 is output and supplied to the bases of the differential transistors 5563 and 5564. The detection signals E1, F1, G1 change smoothly with the rotational movement of the field unit 4510, and are three-phase signals having an electrical phase difference of 120 degrees.

Transistor 554 of switching generator 5502
0,5541,5542,5543,5544,554
5, 5546, 5547, 5548, and 5549 form a current mirror, and a current value proportional to the feedback current signal Ib flows in. The differential transistors 5551 and 5552 are
The current value of the transistor 5542 is distributed to the collector side in response to the detection signals E1 and E2. Transistor 5551
The collector current of the transistor 5553, 5554 is doubled by the current mirror,
A current flowing out / in from the connection end of the transistor 554 and the transistor 5541 is supplied to the resistor 5571, and the switching signal H1 is obtained at the terminal of the resistor 5571. The collector current of the transistor 5552 is doubled by the current mirror of the transistors 5555 and 5556,
The current signal I1 flowing out / in from the connection end of the transistor 6 and the transistor 5543 is supplied to the switching corrector 5503. Similarly, the differential transistors 5557 and 5558 distribute the current value of the transistor 5545 to the collector side in response to the detection signals F1 and F2. The collector current of the transistor 5557 is doubled by the current mirror of the transistors 5559 and 5560,
The current flowing out and in from the connection end of the transistor 5544 is supplied to the resistor 5572, and the switching signal H2 is obtained at the terminal of the resistor 5572.

The collector current of the transistor 5558 is doubled by the current mirror of the transistors 5561 and 5562, and the current signal 12 flowing out / in from the connection end of the transistor 5562 and the transistor 5546 is supplied to the switching corrector 5503. Similarly, the differential transistors 5563 and 5564 distribute the current value of the transistor 5548 to the collector side in response to the detection signals G1 and G2. The collector current of the transistor 5563 is doubled by the current mirror of the transistors 5565 and 5566, and the current flowing out / in from the connection end of the transistor 5566 and the transistor 5547 is converted to the resistance 557.
3 and the switching signal H3 is obtained at the terminal of the resistor 5573. The collector current of the transistor 5564 is doubled by the current mirror of the transistors 5567 and 5568, and the transistor 5568 and the transistor 5568 are amplified.
The current signal 13 flowing out / in from the connection terminal 49 is supplied to the switching corrector 5503.

The switching signals H1, H2, H3 become three-phase voltage signals which change smoothly in response to the detection signal and are supplied to the distributor 4531. Current signals I1, I2, I3
Becomes a three-phase current signal that changes smoothly in response to the detection signal and is supplied to the switching corrector 5503. The switching compensator 5503 is a compensation generator 55 that produces the compensation signal K1.
10 and a setting generator 5520 for generating a predetermined signal K0
And a correction comparator 5530 that compares the correction signal K1 with the predetermined signal K0. Correction creator 5510
Is an amplitude current generator 5511 that generates two amplitude current signals that change in proportion to the amplitude of the detection signal, and a harmonic correction signal that is synchronized with the detection signal and that is multiplied by one amplitude current signal to generate a multiplication correction current signal. Multiplication corrector 5512
And a correction output unit 5513 that outputs a correction signal K1 proportional to the combined correction current signal obtained by combining the other amplitude current signal and the multiplication correction current signal. FIG. 32 shows a specific configuration of the correction generator 5510. Amplitude ammeter 5
511 current acquisition circuits 5595, 5596, 5597
Outputs a current signal corresponding to the absolute value of the current signals I1, I2, I3 or a current signal corresponding to the unipolar value, respectively. The specific configuration of the current acquisition circuit is the same as that shown in FIG. 5, and detailed description thereof will be omitted.

Current acquisition circuit 559 of amplitude current device 5511
The output current signals of 5, 5596 and 5597 are combined to form the amplitude current signal Jt. Since the amplitude current signal Jt is a current signal of the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values, the detection signals E1, F
1, it changes in proportion to the amplitude of G1. Transistor 55
The 98, 5599 and 5600 current mirrors output two amplitude current signals Jf and Jg that are proportional to the amplitude current signal Jt. Transistor 560 of multiplication corrector 5512
2, 5603 distribute the current value of the constant current source 5601 to the collector side in response to the detection signals E1 and E2 of the position detection element, and obtain the difference current by the current mirror of the transistors 5604 and 5605.
7, 5608, 5609, 5610, 5611 and resistor 5
Voltage signal S1 responding to the absolute value of the difference current by 661
Get. That is, the voltage signal S1 that responds to the absolute value of the detection signals E1-E2 is generated. Similarly, the detection signal F1-
The voltage signal S2 responsive to the absolute value of F2 is created in the resistor 5662, and the voltage signal S3 responsive to the absolute value of the detection signals G1-G2 is created in the resistor 5663. Transistor 56
64, 5665, 5666, 5667 and diode 56
68 and 5669 compare the voltage signals S1, S2 and S3 with a predetermined voltage value (including 0V) of the constant voltage source 5675, and shunt the amplitude current signal Jf to each collector side in response to the difference voltage. The collector currents of the transistors 5664, 5665, 5666 are combined to create a combined current, and the combined current and the collector current of the transistor 5667 are compared by the current mirror of the transistors 5671, 5672. The current value is input, the current value is reduced to about 1/2, and the current value is output as the multiplication correction current signal Qh (inflow current).

The correction output unit 5513 is a multiplication correction unit 551.
A combined correction current signal is generated by combining the multiplication correction current signal Qh of 2 and the other amplitude current signal Jg of the amplitude current generator 5511, and the resistance 5691 is energized via the current mirror composed of the transistors 5681 and 5682, and the terminal of the resistance 5691. Then, the correction signal K1 is output. Multiplication corrector 5512
The multiplied correction current signal Qh of ## EQU1 ## is responsive to the multiplication result of the voltage signals S1, S2, S3 responsive to the detection signal and the amplitude current signal Jf of the amplitude current device 5511. Transistor 566
With the configurations of 4, 5665, 5666, 5667, the multiplication correction current signal Qh changes in response to the multiplication result of the minimum value of the voltage signals S1, S2, S3 and the amplitude current signal Jf. The minimum value of the voltage signals S1, S2, S3 that responds to the absolute value of the detection signal is a harmonic signal that is synchronized with the detection signal and that changes six times with respect to a change in one cycle of the detection signal. Therefore, the multiplication correction current signal Qh is a harmonic signal having an amplitude proportional to the amplitude current signal Jf and changing 6 times per cycle of the detection signal. Since the correction signal K1 of the correction output device 5513 is proportional to the combined correction current signal Qh of the multiplication correction current signal Qh and the amplitude current signal Jg, it contains a harmonic signal component responsive to the detection signal in a predetermined ratio.

The setting generator 5520 shown in FIG. 31 is composed of a constant current source 5580 and a resistor 5581, and has a predetermined signal K
Outputs 0. The correction comparator 5530 compares the correction signal K1 with the predetermined signal K0 and outputs the feedback current signal Ib of the current amplification circuit 5591 in response to the difference between the two. Thereby, the correction signal K1 proportional to the amplitude of the detection signal is generated by the three-phase current signals I1, I2, I3, and the feedback current signal Ib obtained by amplifying the current corresponding to the comparison result of the correction signal K1 and the predetermined signal K0 is generated. Made The output currents of the current mirrors of the transistors 5540-5549 change in response to the feedback current signal Ib, and the amplitudes of the three-phase current signals I1, I2, I3 and the three-phase switching signals H1, H2, H3 change.
That is, in response to the comparison result of the correction signal and the predetermined signal, 3
A feedback loop is configured to correct the amplitude of the phase switching signal and the magnitude of the correction signal. As a result, the position detector 4521
Regardless of the amplitudes of the detection signals E1, E2, F1, F2, G1, G2 of the current signals I1, I2, I3 and the switching signal H.
The amplitudes of 1, H2 and H3 have a predetermined magnitude corresponding to the predetermined signal K0. The capacitor 5592 compensates the phase of the feedback loop described above. At this time, the correction generator 5
The correction signal K1 of 510 is a voltage signal containing a harmonic signal component that responds to the harmonic signal of the detection signal in a predetermined ratio.
Since the amplitudes of the switching signals H1, H2, H3 change in response to the difference between the correction signal K1 and the predetermined signal K0, the switching signals H1, H2, H3 have a sinusoidal smooth shape having an amplitude corresponding to the predetermined signal K0. Voltage signal. The distributor 4531 of the distributor 4513 and the first driver 4541, the second driver 4542, and the third driver 4543 of the driver 4514 of FIG.
The configuration and operation of are the same as those shown in FIGS. 17 and 18 described above, and detailed description thereof will be omitted.

Command current unit 40 of command unit 4515 of FIG.
The configuration of 50 is similar to that shown in FIG.
The output signal d of the command current device 4050 is connected to the input signal D of the distributor 4531. The operation of the command current device 4050 is
This is similar to the description of FIG. 3 described above, and detailed description will be omitted. Also in the configuration of this embodiment, the correction signal K1 that changes in proportion to the amplitude of the detection signal of the position detector is generated, and the switching signal H is generated in response to the comparison result of the correction signal K1 and the predetermined signal K0.
The amplitudes of 1, H2 and H3 are corrected. As a result, the switching signals H1, H2, H3, the distribution signals M1, M2, M3 and the drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. Further, the correction generator 551 of the switching corrector 5503
At 0, a high frequency signal responsive to the detection signal is obtained, a multiplication correction current signal is generated by multiplying the harmonic signal, and a correction signal K1 including a harmonic signal component responsive to the multiplication correction current signal is included at a predetermined ratio. . By correcting the amplitudes of the switching signals H1, H2, H3 in response to the result of comparison between the correction signal K1 and the predetermined signal K0, it is possible to obtain a switching signal that smoothly changes in a sinusoidal wave in response to the detection signal. Since the distribution signals M1, M2, M3 are generated in response to the multiplication result of the switching signals H1, H2, H3 and the output signal of the command unit, the distribution signals M1, M2, M3 and the drive signal Va,
Vb and Vc smoothly change in a sine wave shape in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly.

Embodiment 7 FIGS. 33 to 35 show the structure of a brushless motor according to Embodiment 7 of the present invention. FIG. 33 shows an overall configuration diagram of the seventh embodiment. In this embodiment, the number of position detecting elements of the position detector is reduced to two in the third embodiment (FIG. 14) described above. As a result, the number of parts in the motor structure portion is reduced, and it becomes easier to manufacture a small motor. The same parts as those in Example 3 described above are designated by the same reference numerals. FIG. 34 shows specific configurations of the position detector 5701, the switching generator 5702, and the switching corrector 5703 of the position portion 4512. Position detecting element 4630 of position detector 5701
A and 4630B correspond to two of the three position detecting elements 4607a, 4607b, and 4607c of FIG. 15 described above, and a voltage is supplied in parallel via the resistor 4631. That is, the number of position detecting elements attached to the stator is 2
It has been reduced to individual pieces. Differential detection signals E1 and E2 corresponding to the detection magnetic field of the field magnet unit 4510 (corresponding to the permanent magnet 4602 in FIG. 15) are output to the output terminal of the position detection element 4630A. Similarly, differential detection signals F1 and F2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 4630B. The detection signals E1 and F1 change smoothly with the rotational movement of the field unit 4510, and E1 and F1 are two-phase signals having an electrical phase difference of 120 degrees. The detection signals E1 and E2 change to opposite phases, and F1 and F2 change to opposite phases. Here, the detection signals E2 and F2 of opposite phase are
Does not count as a new phase number.

Transistor 574 of switching generator 5702
0,5741, 5742,5743, 5744,574
5,5746,5747,5748,5749,575
0 forms a current mirror, and a current value proportional to the feedback current signal Ib flows in. Differential transistors 5751,5
752 distributes the current value of the transistor 5742 to the collector side in response to the detection signals E1 and E2. The collector current of the transistor 5751 is the transistor 5753, 5
The current mirror 754 doubles the current, and the current flowing out and in from the connection end of the transistor 5754 and the transistor 5741 is supplied to the resistor 5771.
The switching signal H1 is obtained at the terminal 71. Transistor 5
The collector current of 752 is transistor 5755,575
The current signal 11 which is amplified twice by the current mirror 6 and flows in and out from the connection end of the transistor 5756 and the transistor 5743 is supplied to the switching corrector 5703. Similarly, differential transistors 5757 and 5758
Is a transistor 574 in response to the detection signals F1 and F2.
The current value of 5 is distributed to the collector side. Transistor 57
The collector current of 57 is transistors 5759 and 5760.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 5760 and the transistor 5744.
The inflowing current is supplied to the resistor 5772, and the switching signal H2 is obtained at the terminal of the resistor 5772. Transistor 5758
The collector current of the transistor 5 is doubled by the current mirror of the transistors 5761 and 5762,
The current signal 12 flowing out / in from the connection end of the transistor 762 and the transistor 5746 is supplied to the switching corrector 5703.

The differential transistors 5763 and 5764 are
In response to the detection signals E1 and E2, the current value of the transistor 5748 is distributed to the collector side, and the differential transistor 576
5, 5766 distributes the current value of the transistor 5749 to the collector side in response to the detection signals F1 and F2. Collector current of transistor 5764 and transistor 576
The collector currents of 6 are combined to form a transistor 5767,
The current mirror of 5768 doubles the current, and supplies the current flowing out / in from the connection end of the transistor 5768 and the transistor 5747 to the resistor 5773.
The switching signal H3 is obtained at the terminal of 773. The collector current of the transistor 5763 and the collector current of the transistor 5765 are combined to form transistors 5769 and 5770.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 5770 and the transistor 5750.
The inflowing current signal 13 is supplied to the switching corrector 5703. In this manner, the two-phase detection signals E1 and F1 are arithmetically combined to generate a three-phase signal.

The switching signals H1, H2, H3 change smoothly in response to the two-phase detection signals, and are electrically substantially 12
It becomes a three-phase voltage signal having a phase difference of 0 degree, and the distributor 4
531 is supplied. The current signals I1, I2, I3 are 2
It smoothly changes in response to the phase detection signal, and becomes a three-phase current signal having an electrical phase difference of substantially 120 degrees,
It is supplied to the switching corrector 5703. Switching compensator 5703
Is a correction generator 4560 for generating the correction signal K1, a setting generator 4570 for generating the predetermined signal K0, and the correction signal K1.
And a correction comparator 4580 for comparing the predetermined signal K0 with the predetermined signal K0. The correction generator 4560 produces an amplitude current signal 456 that produces an amplitude current signal proportional to the amplitude of the detection signal.
1 and a correction output device 4562 that outputs a correction signal K1 proportional to the amplitude current signal. The specific configuration of these is similar to that shown in FIG. 16, and detailed description thereof will be omitted. In the switching generator 5702 and the switching corrector 5703, the three-phase current signals I1, I2, I3 are generated by using the two-phase detection signals, the correction signal K1 proportional to the amplitude of the detection signal is generated, and the correction signal K1 is generated. A feedback current signal Ib is produced in response to the comparison result of the predetermined signal K0 and the predetermined signal K0.
Transistors 5740-5 in response to the feedback current signal Ib
The output current of the current mirror 750 changes, and the three-phase current signals I1, I2, I3 and the three-phase switching signals H1, H
2, the amplitude of H3 changes. That is, a feedback loop is configured to correct the amplitude of the three-phase switching signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the predetermined signal. As a result, the two-phase detection signals E1, E of the position detector 5701 are
2, regardless of the amplitudes of F1, F2, the current signals I1, I
2, I3 and the switching signals H1, H2, H3 have predetermined amplitudes corresponding to the predetermined signal K0.

The command unit 4515 shown in FIG.
551, a multiplication command unit 5705, and a command output unit 4553. The command current unit 4551 and the command output unit 4553 are similar to those shown in FIGS. 19 and 21, respectively, and detailed description thereof will be omitted. FIG. 35 shows a specific configuration of the multiplication command unit 5705. The transistors 5802 and 5803 of the multiplication command unit 5705 distribute the current value of the constant current source 5801 to the collector side in response to the detection signals E1 and E2 of the position detection element, and the transistors 5804 and 5805.
The difference current is calculated by the current mirror of the transistors 5806, 5807, 5808, 5809, 5810,
The voltage signal S1 corresponding to the absolute value of the difference current is obtained by 5811 and the resistor 5861. That is, the detection signals E1-E
A voltage signal S1 responsive to an absolute value of 2 is produced. Similarly, a constant current source 5821 and transistors 5822 to 583 are provided.
1, the resistor 5862 produces a voltage signal S2 in response to the absolute value of the detection signals F1-F2 at the terminal of the resistor 5862. The transistors 5842 and 5843 detect the detection signal E.
1 and E2, the current of the constant current source 5841 is distributed to the collector side, and the transistors 5845 and 5846 distribute the current of the constant current source 5844 to the collector side in response to the detection signals F1 and F2. By the current mirror of the transistors 5847 and 5848, the difference current of the combined current of the collector current of the transistor 5843 and the collector current of the transistor 5846, the combined current of the collector current of the transistor 5842 and the collector current of the transistor 5845 is obtained.

Transistors 5849, 5850, 585
1,5852,5853,5854 and the resistor 5863 produce the voltage signal S3 in response to the absolute value of the difference current. That is, the signal of the third phase is generated from the detection signals of the two phases, and the voltage signal S3 that responds to the absolute value of the signal of the third phase is generated. Transistors 5864, 5865,
5866, 5867 and diodes 5868, 5869
Compares the voltage signals S1, S2, S3 with a predetermined voltage value (including 0 V) of the constant voltage source 5875, and responds to the difference voltage to output the second command current signal P2 of the command current generator 4551 to each collector side. Divert to. Transistors 5864,586
The collector currents of 5, 5866 are combined, the combined current is compared by the current mirrors of transistors 5871, 5872 with the collector current of transistor 5867, and the difference current is input to the current mirrors of transistors 5873, 5874, and the current value is reduced. Reduce to 1/2,
It is output as a multiplication command current signal Q (inflow current).

Multiplication command current signal Q of multiplication command unit 5705
Responds to the multiplication result of the voltage signals S1, S2, S3 responsive to the detection signal and the second command current signal P2 of the command current generator 4551. Transistors 5864,5865,5
With the configuration of 866 and 5867, the voltage signals S1, S2 and
The multiplication command current signal Q changes in response to the multiplication result of the minimum value of S3 and the command current signal P2. The minimum value of the voltage signals S1, S2, S3 that responds to the absolute value of the detection signal is a harmonic signal that is synchronized with the detection signal and that changes six times with respect to a change in one cycle of the detection signal. Therefore, the multiplication command current signal Q is
The harmonic signal has an amplitude proportional to the command current signal P2 and changes 6 times per cycle of the detection signal. Since the output signal D of the command output device 4553 is proportional to the combined command current signal Q of the multiplication command current signal Q and the first command current signal P1,
A harmonic signal component which responds to the detection signal is included in a predetermined ratio. At this time, the output signal D of the command unit 4515 is a current signal including a harmonic signal component that responds to the harmonic signal of the detection signal in a predetermined ratio. The output signal D and the switching signal H1,
The distribution signals M1, M2, M are calculated according to the multiplication result of H2 and H3.
3 and the drive signals Va, Vb, and Vc are generated, the distribution signal and the drive signal are sine wave smooth three-phase voltage signals. Distributor 453 of distributor 4513 of FIG.
1 and the configuration and operation of the first driver 4541, the second driver 4542, and the third driver 4543 of the drive unit 4514 are the same as those shown in FIGS. To do.

In the configuration of this embodiment, the drive signals for the three-phase coils are generated by using the two-phase detection signals of the position detector. As a result, the number of position detecting elements may be small,
The motor structure can be simplified. Further, a correction signal K1 that changes in proportion to the amplitudes of the two-phase detection signals of the position detector is generated, and the amplitudes of the switching signals H1, H2, H3 are corrected in response to the comparison result of the correction signal K1 and the predetermined signal K0. doing. As a result, the switching signals H1, H2, H3 and the distribution signals M1, M
2, M3 and drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. In addition, a multiplication command device is provided in the command unit to obtain a high frequency signal that responds to the two-phase detection signals, to generate a multiplication command current signal that is multiplied by a harmonic signal, and a harmonic signal component that responds to the multiplication command current signal. To generate an output signal of the command unit including a predetermined ratio. As a result, the distribution signals M1, M2, M3 and the drive signals Va, Vb, Vc are
It smoothly changes in a sinusoidal wave in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly.

Embodiment 8 FIGS. 36 to 38 show the structure of a brushless motor according to Embodiment 8 of the present invention. FIG. 36 shows the overall configuration of the eighth embodiment. In this embodiment, the number of position detecting elements of the position detector is reduced to two in the fifth embodiment (FIG. 27) described above. As a result, the number of parts in the motor structure portion is reduced, and it becomes easier to manufacture a small motor. The same parts as those in Example 5 described above are designated by the same reference numerals. FIG. 37 shows specific configurations of the position detector 5701, the switching generator 5902, and the switching corrector 5903 of the position portion 4512. Position detecting element 4630 of position detector 5701
A and 4630B correspond to two of the three position detecting elements 4607a, 4607b, and 4607c of FIG. 15 described above, and a voltage is supplied in parallel via the resistor 4631. The field detector 45 is provided at the output terminal of the position detection element 4630A.
Differential detection signals E1 and E2 corresponding to the detection magnetic field of 10 (corresponding to the permanent magnet 4602 in FIG. 15) are output. Similarly, differential detection signals F1 and F2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 4630B. The detection signals E1 and F1 change smoothly with the rotational movement of the field unit 4510, and E1 and F1 are two-phase signals having an electrical phase difference of 120 degrees.

Transistor 594 of switching generator 5902
0,5941, 5942, 5943, 5944, 594
5,5946, 5947, 5948, 5949, 595
0 forms a current mirror, and a current value proportional to the feedback current signal Ib flows in. Differential transistors 5951,5
952 distributes the current value of the transistor 5942 to the collector side in response to the detection signals E1 and E2. The collector current of the transistor 5951 is the transistor 5953, 5
The current mirror 954 doubles the current, and the current flowing out and in from the connection end of the transistor 5954 and the transistor 5941 is supplied to the resistor 5971.
The switching signal H1 is obtained at the terminal 71. Transistor 5
The collector current of 952 is the transistors 5955 and 595.
The current signal 11 that is amplified twice by the current mirror 6 and flows out / in from the connection end of the transistor 5956 and the transistor 5943 is supplied to the switching corrector 5903. Similarly, differential transistors 5957 and 5958
Is a transistor 594 in response to the detection signals F1 and F2.
The current value of 5 is distributed to the collector side. Transistor 59
The collector current of 57 is transistor 5959, 5960.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 5960 and the transistor 5944.
The inflowing current is supplied to the resistor 5972, and the switching signal H2 is obtained at the terminal of the resistor 5972.

The collector current of the transistor 5958 is doubled by the current mirror of the transistors 5961 and 5962, and the current signal 12 flowing out / in from the connection end of the transistor 5962 and the transistor 5946 is supplied to the switching corrector 5903. The differential transistors 5963 and 5964 distribute the current value of the transistor 5948 to the collector side in response to the detection signals E1 and E2,
The differential transistors 5965 and 5966 use the detection signal F
In response to 1, F2, the current value of the transistor 5949 is distributed to the collector side. The collector current of the transistor 5964 and the collector current of the transistor 5966 are combined, amplified twice by the current mirror of the transistors 5967 and 5968, and the current flowing out / in from the connection end of the transistor 5968 and the transistor 5947 is supplied to the resistor 5973. Switching signal H to the terminal of resistor 5973
I got 3. The collector current of the transistor 5963 and the collector current of the transistor 5965 are combined, amplified twice by the current mirror of the transistors 5969 and 5970, and the current signal 13 flowing out / in from the connection end of the transistor 5970 and the transistor 5950 is switched and corrected. Is being supplied to. Thus, 2
The phase detection signals E1 and F1 are arithmetically combined to generate a 3-phase signal.

The switching signals H1, H2, and H3 change smoothly in response to the two-phase detection signals, and are electrically substantially 12
It becomes a three-phase voltage signal having a phase difference of 0 degree, and the distributor 4
531 is supplied. The current signals I1, I2, I3 are 2
It smoothly changes in response to the phase detection signal, and becomes a three-phase current signal having an electrical phase difference of substantially 120 degrees,
It is supplied to the switching corrector 5903. Switching compensator 5903
Is a correction generator 5310 for generating the correction signal K1, a setting generator 5905 for generating the predetermined signal K0, and the correction signal K1.
And a predetermined comparator K0. The correction generator 5310 is an amplitude current generator 531 that produces an amplitude current signal proportional to the amplitude of the detection signal.
1 and a correction output device 5312 that outputs a correction signal K1 proportional to the amplitude current signal. The specific configurations of the correction generator 5310 and the correction comparator 5330 are the same as those shown in FIG. 28, and detailed description thereof will be omitted. The setting generator 5905 outputs a setting current device 5321 that outputs two setting current signals, a multiplication setting device 5906 that generates a harmonic signal synchronized with the detection signal, and generates a multiplication setting current signal that is multiplied by one of the setting currents. A setting output device 5323 that outputs a predetermined signal K0 proportional to the combined set current signal obtained by combining the other set current signal and the multiplication set current signal.
It is constituted by. FIG. 38 shows the setting generator 5905.
The following shows a specific configuration. The set current device 5321 is composed of two current sources 5481 and 5482 and outputs two set current signals Pf and Pg.

Transistor 600 of multiplication setter 5906
2, 6003 distribute the current value of the constant current source 6001 to the collector side in response to the detection signals E1 and E2 of the position detection element, and obtain the difference current by the current mirror of the transistors 6004 and 6005.
7,6008,6009,6010,6011 and resistor 6
The voltage signal S1 that responds to the absolute value of the difference current by 061
Get. That is, the voltage signal S1 that responds to the absolute value of the detection signals E1-E2 is generated. Similarly, the constant current source 602
The voltage signal S2 that responds to the absolute value of the detection signals F1-F2 is generated at the terminal of the resistor 6062 by the first transistor 6022 to 6031 and the resistor 6062. Transistors 6042 and 6043 distribute the current of the constant current source 6041 to the collector side in response to the detection signals E1 and E2, and transistors 6045 and 6046 respond to the detection signals F1 and F2 to the current of the constant current source 6044 in the collector side. Distribute to.

Due to the current mirrors of the transistors 6047 and 6048, a combined current of the collector current of the transistor 6043 and the collector current of the transistor 6046, the collector current of the transistor 6042 and the transistor 6
The difference current of the combined current of 045 collector currents is calculated. Transistors 6049, 6050, 6051, 6052,
A voltage signal S3 that responds to the absolute value of the difference current is generated by the resistors 6053 and 6053 and the resistor 6063. That is, the signal of the third phase is generated from the detection signals of the two phases, and the voltage signal S3 that responds to the absolute value of the signal of the third phase is generated. Transistors 6064, 6065, 6066, 60
67 and the diodes 6068 and 6069 form a voltage signal S
1, S2, S3 and a predetermined voltage value of constant voltage source 6075 (0 V
(Including), and responds to the difference voltage to set current generator 5
The setting current signal Pf of 321 is shunted to each collector side.
The collector currents of the transistors 6064, 6065, 6066 are combined to produce a combined current,
The combined current and the collector current of the transistor 6067 are compared by the current mirrors of 071 and 6072, and the difference current is input to the current mirrors of the transistors 6073 and 6074, and the current value is reduced to about 1/2 to set the multiplication set current. It is output as a signal Qg (inflow current).

The setting output unit 5323 is a multiplication setting unit 590.
A combined set current signal obtained by combining the multiplication set current signal Qg of 6 and the other set current signal Pg of the set current unit 1321 is applied to the resistor 5491, and a predetermined signal K is output from the terminal of the resistor 5491.
Outputs 0. The multiplication setting current signal Qg of the multiplication setting unit 5906 is the voltage signals S1 and S corresponding to the two-phase detection signals.
2, S3 and the set current signal Pf of the set current device 5321 are multiplied. Transistors 6064 and 606
The voltage signals S1,
The multiplication setting current signal Qg changes in response to the multiplication result of the minimum value of S2 and S3 and the setting current signal Pf. The minimum value of the voltage signals S1, S2, S3 that responds to the absolute value of the detection signal is
6 in synchronization with the detection signal
It is a harmonic signal that changes once. Therefore, the multiplication setting current signal Qg is a harmonic signal having an amplitude proportional to the setting current signal Pf and changing 6 times per cycle of the detection signal.
The predetermined signal K0 of the setting output device 5323 is proportional to the combined setting current signal of the multiplication setting current signal Qg and the setting current signal Pg, and contains a harmonic signal component that responds to the detection signal in a predetermined ratio.

The correction comparator 5330 of FIG. 37 compares the correction signal K1 with the predetermined signal K0 and outputs the feedback current signal Ib of the current amplification circuit in response to the difference between the two. As a result, the three-phase current signals I1, I2, I3 generate the correction signal K1 proportional to the amplitude of the two-phase detection signal, and the feedback current signal Ib corresponding to the comparison result of the correction signal K1 and the predetermined signal K0 is generated. To be The output currents of the current mirrors of the transistors 5940 to 5950 change in response to the feedback current signal Ib, and the amplitudes of the three-phase current signals I1, I2, I3 and the three-phase switching signals H1, H2, H3 change. That is, a feedback loop is configured to correct the amplitude of the three-phase switching signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the predetermined signal. As a result, regardless of the amplitudes of the two-phase detection signals E1, E2, F1, F2 of the position detector 5701,
Current signals I1, I2, I3 and switching signals H1, H2, H3
Has a predetermined magnitude corresponding to the predetermined signal K0.
At this time, the predetermined signal K0 of the setting generator 5905 is a voltage signal including a predetermined ratio of the harmonic signal component that responds to the harmonic signal of the detection signal. Since the amplitudes of the switching signals H1, H2, H3 change in response to the predetermined signal K0, the switching signals H1, H2, H3 are sine wave-shaped smooth voltage signals having the amplitude corresponding to the predetermined signal K0. The first of the distributor 4531 of the distributor 4513 and the drive unit 4514 of FIG.
Driver 4541, second driver 4542, third driver 45
The configuration and operation of 43 are the same as those shown in FIGS. 17 and 18 described above, and detailed description thereof will be omitted.

The configuration of the command current unit 4050 of the command unit 4515 of FIG. 36 is the same as that shown in FIG. The output signal d of the command current unit 4050 is the distributor 453.
1 is connected to the input signal D. The operation of the command current device 4050 is the same as the above-described description of FIG. 3, and detailed description thereof will be omitted. In the configuration of the present embodiment, the drive signals for the three-phase coils are produced using the two-phase detection signals of the position detector. As a result, the number of position detecting elements may be small and the motor structure can be simplified. Further, a correction signal K1 that changes in proportion to the amplitudes of the two-phase detection signals of the position detector is generated, and the amplitudes of the switching signals H1, H2, H3 are corrected in response to the comparison result of the correction signal K1 and the predetermined signal K0. doing. As a result, the switching signals H1, H2, H3 and the distribution signals M1, M
2, M3 and drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. In addition, a multiplication setting unit 5906 is provided in the setting creation unit 5905 to obtain a high frequency signal that responds to the two-phase detection signals, create a multiplication setting current signal that is multiplied by a harmonic signal, and set a harmonic that responds to the multiplication setting current signal. A predetermined signal K0 containing a wave signal component at a predetermined ratio is produced. As a result, the distribution signals M1, M2, M3 and the drive signal V
a, Vb, and Vc smoothly change in a sine wave shape in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly.

Embodiment 9 FIGS. 39 to 41 show the structure of a brushless motor according to Embodiment 9 of the present invention. FIG. 39 shows an overall configuration diagram of the ninth embodiment. In this embodiment, the number of position detecting elements of the position detector is reduced to two in the sixth embodiment (FIG. 30) described above. As a result, the number of parts in the motor structure portion is reduced, and it becomes easier to manufacture a small motor. The same parts as those in Example 6 described above are denoted by the same reference numerals. FIG. 40 shows a specific configuration of the position detector 5701, the switching generator 6102, and the switching corrector 6103 of the position section 4512. Position detecting element 4630 of position detector 5701
A and 4630B correspond to two of the three position detecting elements 4607a, 4607b, and 4607c of FIG. 15 described above, and a voltage is supplied in parallel via the resistor 4631. The field detector 45 is provided at the output terminal of the position detection element 4630A.
Differential detection signals E1 and E2 corresponding to the detection magnetic field of 10 (corresponding to the permanent magnet 4602 in FIG. 15) are output. Similarly, differential detection signals F1 and F2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 4630B. The detection signals E1 and F1 change smoothly with the rotational movement of the field unit 4510, and E1 and F1 are two-phase signals having an electrical phase difference of 120 degrees.

Transistor 614 of switching generator 6102
0, 6141, 6142, 6143, 6144, 614
5,6146, 6147, 6148, 6149, 615
0 forms a current mirror, and a current value proportional to the feedback current signal Ib flows in. Differential transistors 6151,6
The 152 distributes the current value of the transistor 6142 to the collector side in response to the detection signals E1 and E2. The collector current of the transistor 6151 is equal to that of the transistors 6153, 6
The current mirror 154 doubles the current and supplies the current flowing out / in from the connection end of the transistor 6154 and the transistor 6141 to the resistor 6171.
The switching signal H1 is obtained at the terminal 71. Transistor 6
The collector current of the transistor 152 is the transistors 6155 and 615.
A current signal 11 which is amplified twice by the current mirror 6 and flows out / in from the connection end of the transistor 6156 and the transistor 6143 is supplied to the switching corrector 6103. Similarly, the differential transistors 6157 and 6158
Is a transistor 614 in response to the detection signals F1 and F2.
The current value of 5 is distributed to the collector side. Transistor 61
The collector current of 57 is the transistor 6159, 6160.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 6160 and the transistor 6144.
The inflowing current is supplied to the resistor 6172, and the switching signal H2 is obtained at the terminal of the resistor 6172.

The collector current of the transistor 6158 is doubled by the current mirror of the transistors 6161 and 6162, and the current signal 12 flowing out / in from the connection end of the transistor 6162 and the transistor 6146 is supplied to the switching corrector 6103. The differential transistors 6163 and 6164 distribute the current value of the transistor 6148 to the collector side in response to the detection signals E1 and E2,
The differential transistors 6165 and 6166 have a detection signal F.
In response to 1 and F2, the current value of the transistor 6149 is distributed to the collector side. The collector current of the transistor 6164 and the collector current of the transistor 6166 are combined and doubled by the current mirror of the transistors 6167 and 6168, and the current flowing out / in from the connection end of the transistor 6168 and the transistor 6147 is supplied to the resistor 6173. Switching signal H to the terminal of resistor 6173
I got 3. The collector current of the transistor 6163 and the collector current of the transistor 6165 are combined, amplified twice by the current mirror of the transistors 6169 and 6170, and the current signal 13 flowing out / in from the connection end of the transistor 6170 and the transistor 6150 is switched and corrected. Is being supplied to. Thus, 2
The phase detection signals E1 and F1 are arithmetically combined to generate a 3-phase signal.

The switching signals H1, H2, and H3 change smoothly in response to the two-phase detection signals, and are electrically substantially 12
It becomes a three-phase voltage signal having a phase difference of 0 degree, and the distributor 4
531 is supplied. The current signals I1, I2, I3 are 2
It smoothly changes in response to the phase detection signal, and becomes a three-phase current signal having an electrical phase difference of substantially 120 degrees,
It is supplied to the switching corrector 6103. Switching compensator 6103
Is a correction generator 6105 for generating the correction signal K1, a setting generator 5520 for generating the predetermined signal K0, and the correction signal K1.
And a correction comparator 5530 for comparing the predetermined signal K0 with the predetermined signal K0. The correction generator 6105 generates an amplitude current generator 5511 that produces two amplitude current signals proportional to the amplitude of the detection signal, and a multiplication correction current signal that produces a harmonic signal synchronized with the detection signal and multiplies it by one of the amplitude current signals. It is composed of a multiplication corrector 6106 to be produced and a correction output device 5513 which outputs a correction signal K1 proportional to the combined correction current signal obtained by combining the other amplitude current signal and the multiplied correction current signal. FIG. 41 shows a specific configuration of the correction generator 6105. Current acquisition circuit 559 of amplitude current device 5511
5, 5596 and 5597 are current signals I1 and I, respectively.
2, a current signal corresponding to the absolute value of I3 or a current signal corresponding to a unipolar value is output. The specific configuration of the current acquisition circuit is the same as that shown in FIG. 5, and detailed description thereof will be omitted. Current acquisition circuit 559 of amplitude current device 5511
The output current signals of 5, 5596 and 5597 are combined to form the amplitude current signal Jt. Since the amplitude current signal Jt is a current signal of the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values, the detection signals E1, F1
Changes in proportion to the amplitude of. Transistor 5598,5
The current mirrors of 599 and 5600 use the amplitude current signal J
Two amplitude current signals Jf and Jg proportional to t are output.

Transistor 620 of multiplication corrector 6106
Reference numerals 2 and 6203 distribute the current value of the constant current source 6201 to the collector side in response to the detection signals E1 and E2 of the position detection element, obtain the difference current by the current mirrors of the transistors 6204 and 6205, and obtain the transistors 6206 and 620.
7, 6208, 6209, 6210, 6211 and resistor 6
The voltage signal S1 that responds to the absolute value of the difference current by 261
Get. That is, the voltage signal S1 that responds to the absolute value of the detection signals E1-E2 is generated. Similarly, the constant current source 622
The voltage signal S2 that responds to the absolute value of the detection signals F1-F2 is generated at the terminal of the resistor 6262 by the 1, transistors 6222 to 6231 and the resistor 6262. The transistors 6242 and 6243 distribute the current of the constant current source 6241 to the collector side in response to the detection signals E1 and E2, and the transistors 6245 and 6246 respond to the detection signals F1 and F2 and the current of the constant current source 6244 to the collector side. Distribute to. By the current mirror of the transistors 6247 and 6248, the combined current of the collector current of the transistor 6243 and the collector current of the transistor 6246 and the transistor 6
A difference current between the combined current of the collector current of 242 and the collector current of the transistor 6245 is obtained. Transistor 62
49, 6250, 6251, 6252, 6253, 62
The voltage signal S3 corresponding to the absolute value of the difference current is generated by 54 and the resistor 6263. That is, the signal of the third phase is generated from the detection signals of the two phases, and the voltage signal S3 that responds to the absolute value of the signal of the third phase is generated. The transistors 6264, 6265, 6266, 6267 and the diodes 6268, 6269 compare the voltage signals S1, S2, S3 with a predetermined voltage value (including 0V) of the constant voltage source 6275, and respond to the difference voltage to generate an amplitude current meter. The amplitude current signal Jf of 5511 is shunted to each collector side. Transistor 6
The collector currents of 264, 6265, and 6266 are combined to produce a combined current, which results in transistors 6271 and 627.
2 current mirror and combined current and transistor 6
267 collector currents are compared, and the difference current is input to the current mirrors of the transistors 6273 and 6274,
The current value is reduced to about 1/2 and output as a multiplication correction current signal Qh (inflow current).

The correction output device 5513 is a multiplication correction device 610.
The combined correction current signal Qh of 6 and the other amplitude current signal Jg of the amplitude current unit 5511 are combined to generate a combined correction current signal, and the combined correction current signal is supplied to the resistor 5691 via the current mirrors of the transistors 5681 and 5682.
The correction signal K1 is output from the terminal of the resistor 5691. The multiplication correction current signal Qh of the multiplication corrector 6106 is responsive to the multiplication result of the voltage signals S1, S2, S3 responsive to the two-phase detection signals and the correction current signal Jf of the amplitude rectifier 5511. Transistors 6264, 6265, 6266, 62
With the configuration of 67, the multiplication correction current signal Qh changes in response to the multiplication result of the amplitude current signal Jf and the minimum value of the voltage signals S1, S2, S3. The minimum value of the voltage signals S1, S2, S3 responsive to the absolute value of the detection signal is synchronized with the detection signal,
It is a harmonic signal that changes six times with respect to one cycle of the detection signal. Therefore, the multiplication correction current signal Qh is a harmonic signal having an amplitude proportional to the amplitude current signal Jf and changing 6 times per cycle of the detection signal. Correction output device 5513
The correction signal K1 is proportional to the combined correction current signal Qh of the multiplication correction current signal Qh and the amplitude current signal Jg, and contains a harmonic signal component that responds to the detection signal in a predetermined ratio. FIG.
The setting generator 5520 generates a predetermined signal K0 with a constant current source that generates a setting current signal and a resistor. The correction comparator 5530 compares the correction signal K1 with the predetermined signal K0, and switches the feedback current signal Ib in response to the comparison result.
Supply to 102. The specific configuration of these is similar to that shown in FIG. 31, and detailed description thereof will be omitted.

As a result, the three-phase current signals I1 and I
A correction signal K1 proportional to the amplitudes of the two-phase detection signals is generated by 2 and I3, and a feedback current signal Ib corresponding to the comparison result of the correction signal K1 and the predetermined signal K0 is generated. The output currents of the current mirrors of the transistors 6140 to 6150 change in response to the feedback current signal Ib, and the three-phase current signal I
1, I2, I3 and 3-phase switching signals H1, H2, H3
The amplitude of changes. That is, a feedback loop is configured to correct the amplitude of the three-phase switching signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the predetermined signal. as a result,
Two-phase detection signals E1, E2, F of the position detector 5701
Current signals I1, I2, I3 regardless of the amplitudes of F1, F2
The amplitudes of the switching signals H1, H2 and H3 have a predetermined magnitude corresponding to the predetermined signal K0. At this time, the correction generator 61
The correction signal K1 of 05 is a voltage signal containing a harmonic signal component that responds to the harmonic signal of the detection signal in a predetermined ratio. Since the amplitudes of the switching signals H1, H2 and H3 change in response to the difference between the correction signal K1 and the predetermined signal K0, the switching signal H
1, H2 and H3 are sinusoidal smooth voltage signals having an amplitude corresponding to the predetermined signal K0. Distribution unit 4 of FIG. 39
The configuration and operation of the distributor 4531 of 513 and the first driver 4541, the second driver 4542, and the third driver 4543 of the driving unit 4514 are the same as those shown in FIGS. Description is omitted. The configuration of the command current device 4050 of the command unit 4515 of FIG. 39 is the same as that shown in FIG. 3 described above. The output signal d of the command current device 4050 is connected to the input signal D of the distributor 4531. The operation of the command current device 4050 is the same as the above-described description of FIG. 3, and detailed description thereof will be omitted.

In the structure of this embodiment, the drive signals for the three-phase coils are generated by using the two-phase detection signals of the position detector. As a result, the number of position detecting elements may be small,
The motor structure can be simplified. Further, a correction signal K1 that changes in proportion to the amplitudes of the two-phase detection signals of the position detector is generated, and the amplitudes of the switching signals H1, H2, H3 are corrected in response to the comparison result of the correction signal K1 and the predetermined signal K0. doing. As a result, the switching signals H1, H2, H3 and the distribution signals M1, M
2, M3 and drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. In addition, a multiplication correction unit 6106 is provided in the correction creation unit 6105 to obtain a high frequency signal that responds to the two-phase detection signals, generate a multiplication correction current signal that is multiplied by a harmonic signal, and generate a harmonic correction response to the multiplication correction current signal. A correction signal K1 containing a predetermined ratio of wave signal components is produced. As a result, the distribution signals M1, M2, M3 and the drive signal V
a, Vb, and Vc smoothly change in a sine wave shape in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly.

Embodiment 10 FIGS. 42 to 43 show the structure of a brushless motor according to Embodiment 10 of the present invention. In the tenth embodiment, the above-mentioned third embodiment is used.
In FIG. 14, the first driver 63 of the driving unit 4514 is shown.
01, the second driver 6302, and the third driver 6303 are configured as PWM drive (pulse width modulation drive) to drive the drive unit 45.
We are trying to save 14 power. Incidentally, the above-mentioned Example 48
The same parts as those shown in are attached with the same numbers. FIG.
3 shows specific configurations of the first driver 6301, the second driver 6302, and the third driver 6303 of the driving unit 4514.
The comparator 6321 of the first driver 6301 compares the triangular wave signal Nt generated by the triangular wave generation circuit 6310 with the distribution signal M1, and outputs the pulse width P corresponding to the distribution signal M1.
Produces a WM signal W1. In response to the level of the PWM signal W1, the driving transistors 6322 and 6323 are complementarily turned on / off to drive the driving transistors 6322 and 6323.
PW by 323 and driving diodes 6324 and 6325
The drive signal Va that digitally changes in response to the M signal W1 is supplied to the power supply terminal of the coil 4511A. Similarly, the comparator 6331 of the second driver 6302 compares the triangular wave signal Nt generated by the triangular wave generating circuit 6310 with the distribution signal M2, and generates the PWM signal W2 having a pulse width corresponding to the distribution signal M2. In response to the level of the PWM signal W2, the drive transistors 6332 and 6333 are complementarily turned on / off to drive the drive transistor 633.
2, 6333 and the drive diodes 6334 and 6335 supply the drive signal Vb that digitally changes in response to the PWM signal W2 to the power supply terminal of the coil 4511B.
Similarly, the comparator 6341 of the third driver 2303
Is the triangular wave signal Nt generated by the triangular wave generation circuit 6310.
And the distribution signal M3 are compared with each other to generate a PWM signal W3 having a pulse width corresponding to the distribution signal M3. Drive transistors 6342 and 6343 in response to the level of the PWM signal W3
Driving the transistor 6
342, 6343 and drive diodes 6344, 6345
The drive signal Vc that changes digitally in response to the PWM signal W3 is supplied to the power supply terminal of the coil 4511C.

The position portion 4512 and the distribution portion 4513 in FIG.
The configuration and operation of the command unit 4515 and the command unit 4515 are the same as those in the third embodiment.
The detailed description is omitted here. In this embodiment, the first driver 6301, the second driver 6302, and the third driver 6303 of the drive unit 4512 are distributed signals M1 and M.
P in which PWM operation is performed in response to 2, M3 and power is amplified
The WM drive signals Va, Vb, Vc are supplied to the three-phase coil 4511.
A, 4511B, 4511C. This allows
While supplying sufficient drive power to the three-phase coil, power loss in the drive unit 4514 is significantly reduced. That is, the power loss in the drive transistor and the drive diode is significantly reduced. As a result, a brushless motor with high power efficiency is obtained. Note that the first driver 6301, the second driver 6302, and the third driver 6303 shown in this embodiment.
Can be applied to the driver of each of the above-described examples, and can reduce the power loss in each of the embodiments.

Embodiment 11 FIGS. 44 to 50 show a brushless motor according to Embodiment 11 of the present invention. FIG. 44 shows an overall configuration diagram. The field magnet portion 7010 of FIG. 44 is attached to a rotor or a moving body, forms a plurality of field magnetic poles by the magnetic flux generated by the permanent magnet magnetic poles, and generates the field magnetic flux. Three-phase coil 701
1A, 7011B, and 7011C are attached to a stator or a fixed body, and are electrically displaced by a predetermined angle (corresponding to 120 degrees) with respect to the linkage with the magnetic flux generated by the field magnet portion 3010. It should be noted that the diagonal cross marks on the line in FIG. 44 mean a plurality of lines. FIG. 45 shows the field part 7010 and the three-phase coils 7011A, 7011B, 7
A specific configuration of 011C is shown. An annular permanent magnet 7102 attached to the inside of the rotor 7101 is magnetized to have four poles on the inner surface and the end surface.
0 is formed. An armature iron core 7103 is arranged at a stator position facing the magnetic poles of the permanent magnet 7102, and the armature iron core 7103 has three salient pole portions 7104a, 7104.
b, 7104c are mechanically provided at intervals of 120 degrees, and winding grooves 7106a, 7106 are formed between the salient pole portions.
b, 7106c, the three-phase coils 7105a, 7105a, 7
105b, 7105c (three-phase coil 7011 in FIG. 44)
A, 7011B, 7011C) correspond to each salient pole portion 710.
4a, 7104b, 7104c are respectively wound. The coils 7105a, 7105b, and 7105c are electrically connected to each other with respect to the interlinkage magnetic flux from the permanent magnet 7102.
There is a phase difference of degrees. Here, 1 of N pole and S pole
A mechanical angle of 180 degrees for a set corresponds to electrical 360 degrees.
The stator has three position detecting elements 7107a and 7107.
b, 7107c (for example, a Hall element that is a magnetoelectric conversion element) is arranged to detect a magnetic pole on the end surface of the permanent magnet 7102, thereby detecting a three-phase detection signal corresponding to the relative position of the field part and the coil. I am trying to get it. By rotating the phase of the coil and the position detection element by 90 degrees in terms of electrical angle, and applying a drive signal of the same phase as the detection signal of the position detection element to the coil, a rotational force in a predetermined direction can be obtained.

The command unit 7015 shown in FIG.
50, which produces an output current signal in response to the command signal R, and which is used by the distribution correction unit 7032 of the distribution unit 7013.
To supply. FIG. 46 shows a specific configuration of the command current device 7050. In the circuit to which + Vcc and -Vcc are applied (+ Vcc = 9V, -Vcc = -9V), the transistors 7121 and 7122 and the resistors 7123 and 7124 form a differential circuit, and in response to the command signal R, the constant current source 7120.
Current value is distributed to the collector side of the transistors 7121 and 7122. The collector currents of the transistors 7121 and 7122 are compared by the current mirror of the transistors 7125 and 7126, and the difference current is calculated.
An output current signal d is obtained by outputting the light through a 7,7128 cant mirror. Here, when the command signal R becomes smaller than the ground potential 0V, the output current signal d becomes large.
The position unit 7012 in FIG. 44 is configured by a position detector 7021, and supplies the detection signal of the position detection element of the position detector 7021 to the distribution generator 7031 of the distribution unit 7013.

The position detector 70 of the position portion 7012 is shown in FIG.
21 and the specific configuration of the distribution generator 7031 and the distribution corrector 7032 of the distribution unit 7032. Position detector 7021
Position detecting elements 7130A, 7130B, 7130C
Is the position detecting elements 7107a, 7107b, 7 of FIG.
The voltage is supplied in parallel via the resistor 7131, which corresponds to 107 c. A field portion 7010 (corresponding to the permanent magnet 7102 in FIG. 45) is provided at the output terminal of the position detection element 7130A.
Differential detection signals e1 and e2 corresponding to the detection magnetic field of
It is supplied to the base of 1,7152. Differential detection signals f1 and f2 corresponding to the detection magnetic field of the field unit 7010 are output to the output terminal of the position detection element 7130B, and are supplied to the bases of the differential transistors 7157 and 7158. The field detector 70 is provided at the output terminal of the position detecting element 7130C.
Differential detection signals g1 and g2 corresponding to the detection magnetic field of 10 are output and supplied to the bases of the differential transistors 7163 and 7164. The detection signals e1, f1, g1 and e2, f2, g2 change smoothly (analogously) with the rotational movement of the field unit 7010, and become a three-phase signal having a phase difference of 120 degrees electrically. There is. The detection signals e1 and e2 change to opposite phases, f1 and f2 change to opposite phases, and g1 and g2 change to opposite phases. Here, the reverse phase signal is not counted as a new phase number.

Transistor 714 of distribution creator 7031
0, 7141, 7142, 7143, 7144, 714
5, 7146, 7147, 7148, and 7149 form a current mirror, and output (inflow) a current value proportional to the feedback current signal ib. Differential transistors 7151,71
52 is a transistor 7 in response to the detection signals e1 and e2.
The current value of 142 is distributed to the collector side. The collector current of the transistor 7151 is the same as that of the transistors 7153 and 71.
The current that is amplified by a current mirror of 54 and flows out and flows in from the connection end of the transistor 7154 and the transistor 7141 is supplied to the resistor 7171.
A distributed signal m1 is produced at the terminal 1 Transistor 71
The collector current of 52 is the transistor 7155, 7156.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 7156 and the transistor 7143.
The inflowing current signal i1 is supplied to the distribution corrector 7032. Similarly, differential transistors 7157 and 7158
Is a transistor 714 in response to the detection signals f1 and f2.
The current value of 5 is distributed to the collector side.

The collector current of the transistor 7157 is doubled by the current mirror of the transistors 7159 and 7160, and the current flowing out / in from the connecting end of the transistor 7160 and the transistor 7144 is transferred to the resistor 71.
72 to generate a distribution signal m2 at the terminal of the resistor 7172. The collector current of the transistor 7158 is 2 by the current mirror of the transistors 7161 and 7162.
Doubled, transistor 7162 and transistor 7
The current signal i2 flowing out / in from the connection end of 146 is supplied to the distribution corrector 7032. Similarly, the differential transistors 7163 and 7164 distribute the current value of the transistor 7148 to the collector side in response to the detection signals g1 and g2. The collector current of the transistor 7163 is doubled by the current mirror of the transistors 7165 and 7166.
The current flowing out and in from the connection end of 47 is supplied to the resistor 7173, and the distribution signal m3 is produced at the terminal of the resistor 7173. The collector current of the transistor 7164 is doubled by the current mirror of the transistors 7167 and 7168, and the transistor 7168 and the transistor 714 are amplified.
The current signal i3 flowing out / in from the connection terminal 9 is supplied to the distribution corrector 7032.

The distribution signals m1, m2, m3 become three-phase voltage signals that change smoothly in response to the detection signal, and the first driver 7041 and the second driver 704 of the driving unit 7014 are provided.
2, supplied to the third driver 7043. Current signal i1,
i2 and i3 change smoothly in response to the detection signal 3
It becomes a phase current signal and is supplied to the distribution corrector 7032 (here, the distribution signals m1, m2, m3 and the current signal i).
1, i2, i3 change in the opposite phase, but may change in the same phase). The distribution corrector 7032 uses the correction signal k
1, a correction generator 7060 that generates 1, a command-side generator 7070 that generates a command-side signal k0 that responds to the output signal d of the command unit 7015, and a correction comparator 7080 that compares the correction signal k1 with the command-side signal k0. ing. The correction generator 7060 includes an amplitude current generator 7061 that generates an amplitude current signal jt that changes in proportion to the amplitude of the detection signal.
It is composed of a correction output unit 7062 which produces a correction signal k1 proportional to the amplitude current signal jt. The amplitude current generator 7061 is a current acquisition circuit 7195, 7196, 719 to which the three-phase current signals i1, i2, i3 are input, respectively.
7 and diodes 7184, 7185, 71 for current combination
It is composed of 86. Current acquisition circuit 7195
7196 and 7197 are current signals i1, i2 and i2, respectively.
The current signal corresponding to the absolute value of i3 or the current signal corresponding to the unipolar value is output.

FIG. 48 shows a specific configuration of the current acquisition circuit 7195. When the switch SW is on the a side, the absolute value of the current signal i1 is created by the transistors 7200, 7201, 7202, 7203, and the transistor 72
The current signal j1 corresponding to the absolute value is output (flowed in) through the current mirrors 04 and 7205. When SW is on the b side, the current signal j1 corresponding to the unipolar value of the current signal i1 is output. The configurations of the current acquisition circuits 7196 and 7197 are similar. The current acquisition circuit may be configured to obtain an output current signal corresponding to the absolute value of the input current signal, or may be configured to obtain an output current signal corresponding to the unipolar value of the input current signal. Good. Amplitude ammeter 70
The output current signals of the current acquisition circuits 7195, 7196, 7197 of 61 are diodes 7184, 7185, 718.
6 to obtain the amplitude current signal jt. Since the amplitude current signal jt is a current signal of the added value of the absolute values of the three-phase current signals i1, i2, i3 or the added value of the unipolar values, it changes in proportion to the amplitude of the detection signals e1, f1, g1. To do. The correction output device 7062 supplies the amplitude current signal jt to the resistor 7183 and supplies the correction signal k1 to the terminal of the resistor 7183.
To produce Therefore, the amplitude current signal jt and the correction signal k1 change in proportion to the amplitude of the detection signal. The command side generator 7070 supplies the output current signal d of the command unit 7015 to the resistor 7175 via the current mirrors of the transistors 7176 and 7177, and generates the command side signal k0 at the terminal of the resistor 7175. That is, the command side signal k0 is generated by converting the output current signal d of the command unit 7015 into a voltage. Therefore, the command side signal k0 is proportional to the output current signal d and substantially corresponds to the output signal of the command unit 7015.

The correction comparator 7080 outputs the correction signal k1 and the command side signal k0 to the transistors 7187, 7188, 71.
89, 7190, and the difference current corresponding to the difference between the two is input to the current amplification circuit 7191. Current amplifier 7
191 outputs a feedback current signal ib obtained by amplifying the input current. That is, the correction comparator 7080 substantially compares the correction signal k1 with the output signal of the command unit 7015, and outputs the feedback current signal ib responsive to the comparison result. In this way, the correction signal k1 responsive to the amplitudes of the three-phase current signals i1, i2, i3 proportional to the detection signals e1, f1, g1
, A command-side signal k0 that responds to the command signal of the command unit, a feedback current signal ib that responds to the comparison result of the correction signal k1 and the command-side signal k0, and a transistor 7140 to respond to the feedback current signal ib. By changing the output current of the current mirror 7149, three-phase current signals i1, i2, i
The amplitudes of the three-phase and three-phase distribution signals m1, m2, m3 are changed. As a result, a feedback loop is configured to correct the amplitude of the three-phase distribution signal and the magnitude of the correction signal in response to the comparison result of the correction signal and the command side signal. As a result, the current signals i1, i2, i3 and the distribution signal m1, regardless of the amplitudes of the detection signals e1, f1, g1 of the position detector 7021.
The amplitudes of m2 and m3 have a predetermined magnitude corresponding to the command side signal k0. The capacitor 7192 compensates the phase of the feedback loop.

The drive unit 7014 shown in FIG. 44 is the first drive unit 70.
41, the second driver 7042, and the third driver 7043, the drive signals Va, Vb, and Vc having voltage waveforms obtained by power-amplifying the distribution signals m1, m2, and m3 of the distribution unit 7013 are 3
Supply to the terminals of the phase coils 7011A, 7011B, 7011C. FIG. 47 shows a first driver 704 of the driving unit 7014.
1, the specific configurations of the second driver 7042 and the third driver 7043 are shown. The distribution signal m1 is input to the non-inverting terminal side of the amplifier 7260 of the first driver 7041, and the resistor 726 is input.
The drive signal Va is generated by amplifying the voltage determined by 1,7262 and is supplied to the power supply terminal of the coil 7011A. Similarly, the distribution signal m2 is output to the amplifier 726 of the second driver 7042.
3 is input to the non-inverting terminal side, and resistors 7264 and 7265 are input.
The voltage determined by is amplified to generate the drive signal Vb, which is supplied to the power supply terminal of the coil 7011B. Similarly, the distribution signal m
3 is input to the non-inverting terminal side of the amplifier 7266 of the third driver 7043, amplifies the voltage determined by the resistors 7267 and 7268 to generate the drive signal Vc, and supplies the drive signal Vc to the power supply terminal of the coil 7011C. The amplifiers 7260, 7263,
The power source voltages of + Vm and -Vm are supplied to the 7266 (+ Vm = 15V, -Vm = -15V).

Drive signals of three phases 7011A, 7011B, and 7011C are energized by drive signals Va, Vb, and Vc, and a driving force in a predetermined direction is generated by electromagnetic action with field unit 7010. FIG. 50 shows a signal waveform for explaining the operation of this embodiment. Position detection elements 7130A and 7130A, 7130A that detect the magnetic field of the field portion 7010 as the field portion 7010 rotates (or moves relative to the three-phase coil).
130B and 7130C are sinusoidal detection signals e1-e.
2, f1-f2, g1-g2 are obtained [see FIG. 50 (a): the horizontal axis is the rotational position]. The distribution generator 7031 and the distribution corrector 7032 change smoothly in response to the detection signal 3
Phase current signals i1, i2, i3 [FIG. 50 (b),
(C), (d)] and three-phase distribution signals m1, m2, m3 are created, and correction signals corresponding to the sum of absolute values of the three-phase current signals i1, i2, i3 or the sum of unipolar values are added. k
1 [FIG. 50 (e): the vertical axis is the negative side is upward], and the feedback loop is operated so that the correction signal k1 matches the command side signal k0. Along with this, in response to the comparison result of the correction signal k1 and the command side signal k0, the distribution signals m1, m2,
The amplitude of m3 is also corrected [FIG. 50 (f)]. Drive unit 70
14 first driver 7041, second driver 7042, third
The driver 7043 receives the distribution signals m1, m2, m3, respectively.
The drive signals Va, Vb, and Vc obtained by power amplification of are supplied to the three-phase coils 7011A, 7011B, and 7011C [FIG.
0 (g)].

With the configuration of this embodiment, a correction signal that changes in proportion to the amplitude of the detection signal is created, and the amplitude of the distribution signal can be easily corrected in response to this correction signal. As a result, even if the amplitude of the detection signal of the position detector 4021 is large or small, the amplitudes of the distribution signals m1, m2, and m3 are the command side signals due to the operations of the distribution generator 7031 and the distribution corrector 7032. It has a predetermined size corresponding to k0. Therefore, the distribution signals m1, m2,
The m3 and the drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. That is, the position detector 7021
Are not affected by the sensitivity variations of the position detecting elements 7130A, 7130B, 7130C, the magnetic field variations of the field unit 7010, and the circuit gain variations of the distribution generator 7031 (the influences are extremely small). Therefore, when speed control or torque control is performed using the brushless motor of the present embodiment, variations in speed control gain and torque control gain between motors are eliminated, and motor control performance during mass production becomes extremely stable. In particular, the control instability phenomenon due to the gain variation of the motor does not occur. Further, if the distribution generator 7031 and the distribution compensator 7032 generate a correction signal corresponding to the addition value of the unipolar values or the addition value of the absolute values of the three-phase current signals, the correction signal changes in proportion to the amplitude of the detection signal. The correction signal to be obtained can be always obtained with a simple circuit configuration, and accurate correction can be performed. Of course, it goes without saying that the circuit configuration for obtaining the correction signal corresponding to the added value of the unipolar values can be simpler than the circuit configuration for obtaining the correction signal corresponding to the added value of the absolute values. In the present embodiment, even if the detection signal of the position detector changes in a smooth sine wave shape, the distribution signal and the drive signal are distorted into a trapezoidal wave shape. Although it is acceptable in many applications, it is preferable to eliminate distortion in order to achieve higher performance.
Next, an embodiment in which this point is improved will be shown.

Embodiment 12 FIGS. 51 to 54 show the structure of a brushless motor according to Embodiment 12 of the present invention. FIG. 51 shows an overall configuration diagram. In the twelfth embodiment, the command unit 7015 shown in FIG.
301, a multiplication commander 7302, and a command output device 7303 are used to generate a distribution signal and a drive signal in a sine wave shape that changes smoothly. The same parts as those in Example 11 described above are denoted by the same reference numerals. The command unit 701 is shown in FIG.
5 shows a specific configuration of the command current unit 7301 of No. 5. The transistors 7321 and 7322 and the resistors 7323 and 7324 shunt the current value of the constant current source 7320 to the collector side of the transistors 7321 and 7322 in response to the command signal R, and the collector currents are compared by the current mirrors of the transistors 7325 and 7326. The difference current is output as two command current signals p1 and p2 via the current mirrors of the transistors 7327, 7328 and 7329. Therefore, the command current unit 7301 produces two command current signals p1 and p2 (p1 and p2 are proportional) in response to the command signal R, and the first command current signal p1 is supplied to the command output unit 7303 and the second command current signal p1 is supplied. The command current signal p2 is the multiplication command unit 730.
2 is supplied.

FIG. 53 shows the multiplication command unit 73 of the command unit 7015.
02 shows a specific configuration. Transistors 7342, 7
343 responds to the detection signals e1 and e2 of the position detection element to distribute the current value of the constant current source 7341 to the collector side, obtain the difference current by the current mirrors of the transistors 7344 and 7345, and the transistors 7346, 7347 and 73.
The voltage signal s1 responsive to the absolute value of the difference current is obtained by 48, 7349, 7350, 7351 and the resistor 7411.
That is, the voltage signal s1 that responds to the absolute value of the detection signals e1-e2 is created. Similarly, the voltage signal s2 responsive to the absolute value of the detection signals f1-f2 is generated in the resistor 7412, and the voltage signal s responsive to the absolute value of the detection signals g1-g2.
3 is created in the resistor 7413. Transistor 7414,
7415, 7416, 7417 are voltage signals s1, s
2, s3 and a predetermined voltage value (including 0 V) of the constant voltage source 7418 are compared, and the command current unit 730 is operated in response to the difference voltage.
The command current signal p2 of 1 is shunted to each collector side. The collector currents of the transistors 7414, 7415, and 7416 are combined to create a combined current, and the transistor 742
The combined current and the collector current of the transistor 7417 are compared by the current mirrors 1 and 7422, and the difference current is output as a multiplication command current signal q via the current mirrors of the transistors 7423 and 7424 (inflow current). The multiplication command current signal q responds to the result of multiplication of the voltage signals s1, s2, s3 responding to the detection signal and the command current signal p2 responding to the command signal. In particular, due to the configuration of the transistors 7414, 7415, 7416, 7417, the multiplication command current signal q changes in response to the multiplication result of the command current signal p2 and the minimum value of the voltage signals s1, s2, s3. Voltage signals s1, s2, which respond to the absolute value of the detection signal
The minimum value of s3 is a harmonic signal that is synchronized with the detection signal and changes six times with respect to a change in one cycle of the detection signal. Therefore, the multiplication command current signal q is a harmonic signal having an amplitude proportional to the command current signal p2 and changing 6 times per cycle of the detection signal.

FIG. 54 shows the command output unit 73 of the command unit 7015.
03 shows a specific configuration. The multiplication command current signal q of the multiplication command device 7302 is input to the current mirrors of the transistors 7431 and 7432, the current value thereof is reduced to about 1/2, and then the first command current signal p of the command current device 7301 is set.
1 is added and combined, and the combined command current signal is output as an output current signal d via the current mirrors of the transistors 7433 and 7434 and the current mirrors of the transistors 7435 and 7436. As a result, the output current signal d of the command unit 7015 responds to the command signal and includes a harmonic signal component in a predetermined ratio. Position part 7012 of FIG.
(Position detector 7021), distribution unit 7013 (distribution creation unit 7031 and distribution correction unit 7032), drive unit 7014 (first driver 7041, second driver 7042, and third driver 7).
The specific configuration and operation of 043) are the same as in FIG.
Since it is similar to that shown in FIG. 49, detailed description will be omitted.

FIG. 55 shows signal waveforms for explaining the operation of this embodiment. Position detection elements 7130A, 7130B, 713 that detect the magnetic field of the field unit 7010 as the field unit 7010 rotates (or moves relative to the three-phase coil).
0C is a sinusoidal detection signal e1-e2, f1-f2, g
1-g2 is obtained [see FIG. 55 (a): the horizontal axis is the rotational position]. For a command signal R having a predetermined value [FIG. 55 (b): the vertical axis is the negative side is upward], the command current unit 73 of the command unit 7015 is used.
01, the multiplication command unit 7302, and the command output unit 7303 cause the output current signal d of the command unit 7015 to include a harmonic signal component in response to the detection signal in a predetermined ratio [FIG. 55 (c)]. Since the command side signal k0 is proportional to the output current signal d, the command side signal k0 also contains a harmonic signal component in response to the detection signal in a predetermined ratio. Distribution creator 703
1 and the distribution corrector 7032 are three-phase current signals i1, which change smoothly in response to the detection signal of the position detector 7021.
i2, i3 [FIG. 55 (d)] and three-phase distribution signals m1, m
2, m3 are created, and three-phase current signals i1, i2, i3
The correction signal k1 [FIG. 55 (e): the vertical axis is the negative side is upward] corresponding to the addition value of the absolute value or the addition value of the unipolar value is obtained so that the correction signal k1 matches the command side signal k0. The feedback loop is operating. Accordingly, in response to the comparison result of the correction signal k1 and the command side signal k0, the distribution signal m
The amplitudes of 1, m2 and m3 are also corrected [FIG. 55 (f)].
As a result, the amplitudes of the distributed signals m1, m2, m3 have a magnitude corresponding to the command side signal k0, and are not affected by the amplitude of the detection signal. First driver 704 of driver 7014
The first, second driver 7042, and third driver 7043 use three-phase coils 7011A, 7011 to generate drive signals Va, Vb, Vc obtained by power-amplifying the distribution signals m1, m2, m3, respectively.
B, supplied to 7011C [FIG. 55 (g)].

With the structure of this embodiment, the distribution signals m1, m2, m3 and the drive signals Va, Vb, Vc are
Position detectors 7130A and 713 of the position detector 7021
0B, 7130C sensitivity variations, field variation 7010 magnetic field variations, and distribution generator 7031 circuit gain variations are no longer affected (the effect is extremely small). Further, the command section produces an output signal that is proportional to the command signal and that includes a harmonic signal component that responds to the harmonic signal of the detection signal in a predetermined ratio. If a distribution signal responsive to the comparison result of the command side signal k0 and the correction signal k1 proportional to this output signal is created, the distribution signals m1, m2, m3 and the drive signals Va, Vb, Vc respond to the detection signal. A sine wave three-phase signal that changes smoothly can be obtained. Therefore,
Distortion of the distribution signal and the drive signal is significantly reduced, a uniform generated torque is obtained, and the motor can be smoothly driven. Further, the command unit creates two command current signals in response to the command signal by the command current device, and creates a multiplication command current signal by multiplying one command current signal by the multiplication command device by the harmonic signal of the detection signal, The output device obtains the output current signal and the command side signal that are the combination of the other command current signal and the multiplication command current signal. As a result, since the transistors 7414, 7415, and 7416 can perform the non-linear differential operation in the multiplication command device, the amplitude variation of the multiplication command current signal q can be reduced even if the detection signal amplitude varies.
It is possible to reduce variations in the ratio of the harmonic signal components included in the output current signal d of the command unit and the command side signal k0. In other words, the structure is strong against variations in sensitivity of the position detection element and variations in the magnetic field of the field unit.

Embodiment 13 FIGS. 56 to 62 show the structure of a brushless motor according to Embodiment 13 of the present invention. In the thirteenth embodiment, the mounting positional relationship between the coil and the position detecting element is shifted by an electrical angle of about 30 degrees, and the position detecting element is arranged between the coils, so that the small motor can be easily manufactured. A drive signal shifted by 30 degrees from the detection signal of the position detection element is applied to the coil in accordance with the phase relationship between the position detection element and the coil. FIG. 56 shows an overall configuration diagram. The field magnet portion 7510 shown in FIG. 56 is attached to a rotor or a moving body, forms a plurality of field magnetic poles by the magnetic flux generated by the permanent magnet magnetic poles, and generates the field magnetic flux. Three-phase coil 751
1A, 7511B, and 7511C are attached to a stator or a fixed body, and are electrically displaced by a predetermined angle (corresponding to 120 degrees) with respect to the linkage with the magnetic flux generated by the field magnet portion 7510.

FIG. 57 shows the field part 7510 and the three-phase coil 75.
11A, 7511B, and 7511C are shown. An annular permanent magnet 7602 attached to the inner side of the rotor 7601 has its inner surface magnetized to have four poles.
Field portion 7510 is formed. An armature iron core 7603 is arranged at a stator position facing the magnetic poles of the permanent magnet 7602, and the armature iron core 7603 has three salient pole portions 7604.
a, 7604b, 7604c are provided at mechanical angle intervals of 120 degrees, and three-phase coils 7605a, 7605b, 76
05c (three-phase coils 7511A, 7511B of FIG. 56,
(Corresponding to 7511C) is each salient pole portion 7604a, 7604
b and 7604c, respectively. Coil 76
05a, 7605b, 7605c are permanent magnets 3602.
There is an electrical phase difference of 120 degrees with respect to the interlinkage magnetic flux. The stator has three position detecting elements 760.
7a, 7607b, 7607c are arranged, and the permanent magnet 7
By detecting the magnetic pole of 602, three-phase detection signals corresponding to the relative positions of the field magnet portion and the coil are obtained. In this embodiment, the phase of the coil and the position detecting element is 1 in terms of electrical angle.
It is offset by 20 degrees. Thereby, each position detecting element can be arranged between each salient pole portion of the armature core so as to detect the magnetic field of the inner surface portion of the permanent magnet, and the motor structure can be made compact.

The command unit 7515 of FIG.
551, the multiplication command unit 7552, and the command output unit 7553, and produces an output current signal containing a harmonic signal component in response to the harmonic component of the detection signal at a predetermined ratio. FIG. 60 shows a specific configuration of the command current unit 7551 of the command unit 7515. Transistors 7821, 7822,
The resistors 7823 and 7824 respond to the command signal R to change the current value of the constant current source 7820 to the transistors 7821 and 7822.
Is shunted to the collector side of the transistors 7825, 782
The collector current is compared by the current mirror of 6,
The difference current is the transistors 7827, 7828, 782.
Two command current signals P1, through the current mirror 9
It is output as P2. Therefore, the command current unit 7551 has two command current signals P1 and P2 in response to the command signal R.
(P1 and P2 are proportional), the first command current signal P1 is supplied to the command output device 7553, and the second command current signal P2 is supplied to the multiplication command device 7552.

FIG. 61 shows the multiplication command unit 75 of the command unit 7515.
A specific configuration of 52 is shown. Transistor 7842,7
843 responds to the detection signals E1 and E2 of the position detecting element to distribute the current value of the constant current source 7841 to the collector side, obtain the difference current by the current mirror of the transistors 7844 and 7845, and obtain the transistors 7846, 7847 and 78.
48, 7849, 7850, 7851 and the resistor 7911 obtain the voltage signal S1 corresponding to the absolute value of the difference current.
That is, the voltage signal S1 that responds to the absolute value of the detection signals E1-E2 is generated. Similarly, the voltage signal S2 that responds to the absolute value of the detection signals F1-F2 is generated in the resistor 7912, and the voltage signal S that responds to the absolute value of the detection signals G1-G2.
3 is created in the resistor 7913. Transistor 7914,
7915, 7916, 7917 are voltage signals S1, S
2, S3 is compared with a predetermined voltage value of the constant voltage source 7918, and the command current signal P2 of the command current generator 7551 is shunted to each collector side in response to the difference voltage. Transistor 791
The collector currents of 4, 7915 and 7916 are combined to create a combined current, and the combined current and the transistor 791 are combined by the current mirror of the transistors 7921 and 7922.
The collector currents of Nos. 7 and 7 are compared, and the difference current is input to the current mirrors of the transistors 7923 and 7924, the current value is reduced to about 1/2, and the multiplication command current signal Q is output (inflow current).

The multiplication command current signal Q responds to the multiplication result of the voltage signals S1, S2, S3 responding to the detection signal and the command current signal P2 responding to the command signal R. In particular, due to the configuration of the transistors 7914, 7915, 7916, 7917, the multiplication command current signal Q changes in response to the multiplication result of the command current signal P2 and the minimum value of the voltage signals S1, S2, S3. Voltage signal S1, which responds to the absolute value of the detection signal
The minimum value of S2 and S3 is a harmonic signal that is synchronized with the detection signal and changes six times with respect to a change in one cycle of the detection signal.
Therefore, the multiplication command current signal Q is a harmonic signal having an amplitude proportional to the command current signal P2 and changing 6 times per cycle of the detection signal. FIG. 62 shows a specific configuration of the command output device 7553 of the command unit 7515. Multiplication commander 755
The multiplication command current signal Q of 2 is the transistor 7931, 79
32 is input to the current mirror, the current direction is inverted, and then added and synthesized with the first command current signal P1 of the command current unit 7551.
933, 7934 current mirror and transistor 79
The output current signal D is output through the current mirrors 35 and 7936. As a result, the output current signal D of the command unit 7515 responds to the command signal and includes a harmonic signal component in a predetermined ratio. The position part 7512 of FIG. 56 is composed of a position detector 7521, and the distribution part 7513 is composed of a distribution generator 7531 and a distribution corrector 7532, which change smoothly in response to the detection signal of the position detection element of the position detector 7521. A distribution signal to be generated is supplied to the driving unit 7514.

FIG. 58 shows a specific configuration of the position detector 7521, the distribution generator 7531, and the distribution corrector 7532.
Position detectors 7630A and 763 of the position detector 7521
0B and 7630C are the position detection elements 7607 of FIG.
a, 7607b, 7607c, and a voltage is supplied in parallel via a resistor 7631. Position detecting element 76
Differential detection signals E1 and E2 corresponding to the detection magnetic field of the field magnet unit 7510 (corresponding to the permanent magnet 7602 in FIG. 57) are output to the output terminal of 30A, and the differential transistors 7651 and 7652 of the distribution generator 7531 are output. Supplied to the base. The field detector 75 is provided at the output terminal of the position detection element 7630B.
Differential detection signals F1 and F2 corresponding to the detection magnetic fields of 10 are output and supplied to the bases of the differential transistors 7657 and 7658. Differential detection signals G1 and G2 corresponding to the detection magnetic field of the field magnet portion 7510 are output to the output terminal of the position detection element 7630C, and the differential transistor 766 is output.
Supplied to the base of 3,7664. Field part 751
With the rotational movement of 0, the detection signals E1, F1, G1 and E2, F2, G2 change smoothly (analogically),
It is a three-phase signal having an electrical phase difference of 120 degrees. The detection signals E1 and E2 change in opposite phases, F1 and F2 change in opposite phases, and G1 and G2 change in opposite phases.

Distributor 7531 Transistor 764
0,7641,7642,7643,7644,764
5, 7646, 7647, 7648, 7649 form a current mirror, and a current value proportional to the feedback current signal Ib flows in. The differential transistors 7651 and 7652 are
The current value of the transistor 7642 is distributed to the collector side in response to the detection signals E1 and E2. Transistor 7651
The collector current of the transistor 765 is amplified twice by the current mirror of the transistors 7653 and 7654.
A current flowing out / in from the connection end of the transistor 654 and the transistor 7641 is supplied to the resistor 7671, and the distribution signal M1 is generated at the terminal of the resistor 7671. The collector current of the transistor 7652 is doubled by the current mirror of the transistors 7655 and 7656,
6 is supplied to the distribution corrector 7532 with the current signal 11 flowing out and flowing in from the connection end of 6 and the transistor 7643. Similarly, the differential transistors 7657 and 7658 distribute the current value of the transistor 7645 to the collector side in response to the detection signals F1 and F2. The collector current of the transistor 7657 is doubled by the current mirror of the transistors 7659 and 7660,
A current flowing out / in from the connection end of the transistor 7644 is supplied to the resistor 7672, and a distribution signal M2 is generated at the terminal of the resistor 7672. The collector current of the transistor 7658 is doubled by the current mirror of the transistors 7661 and 7662, and the current signal 12 that flows in and out from the connection end of the transistor 7662 and the transistor 7646 is supplied to the distribution corrector 7532.

Similarly, the differential transistors 7663 and 76 are
64 is a transistor 7 in response to the detection signals G1 and G2.
The current value of 648 is distributed to the collector side. The collector current of the transistor 7663 is the transistors 7665 and 76
The current mirror 66 supplies the current that is doubled and flows out and flows in from the connection end of the transistor 7666 and the transistor 7647 to the resistor 7673, and the resistor 767 is supplied.
A distributed signal M3 is produced at the terminals of No. 3. Transistor 76
The collector current of 64 is the transistor 7667, 7668
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 7668 and the transistor 7649.
The inflowing current signal 13 is supplied to the distribution corrector 7532.

The distribution signals M1, M2, M3 become three-phase voltage signals that change smoothly in response to the detection signal and are supplied to the drive unit 7514. Current signals I1, I2, I3
Becomes a three-phase current signal that changes smoothly in response to the detection signal and is supplied to the distribution corrector 7532 (here, the distribution signals M1, M2, M3 and the current signals 11, 12,
13 changes in the opposite phase, but may change in the same phase). The distribution corrector 7532 includes a correction creator 7560 that creates a correction signal K1 and a command-side creator 757 that creates a command-side signal K0 that responds to the output signal of the command unit 7515.
0, and a correction comparator 7580 for comparing the correction signal K1 and the command side signal K0. Correction creator 75
Reference numeral 60 denotes an amplitude current generator 7561 that produces an amplitude current signal Jt that changes in proportion to the amplitude of the detection signal, and a correction output device 75 that produces a correction signal K1 that is proportional to the amplitude current signal Jt.
It is constituted by 62. The amplitude current unit 7561 is
It is composed of current acquisition circuits 7695, 7696, 7697 to which the three-phase current signals I1, I2, I3 are respectively inputted and diodes 784, 7685, 7686 for current combination. Current acquisition circuit 7695, 7696, 7
697 outputs a current signal corresponding to the absolute value of the current signals I1, I2, I3 or a current signal corresponding to the unipolar value, respectively. The specific configuration of the current acquisition circuit is shown in FIG.
The detailed description is omitted because it is the same as that shown in FIG.

Current acquisition circuit 769 of amplitude current generator 7561
The output current signals of 5,7696,7697 are combined via the diodes 7684,7685,7686 to obtain the amplitude current signal Jt. Since the amplitude current signal Jt is a current signal of the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values, the detection signals E1, F
1, it changes in proportion to the amplitude of G1. Correction output device 756
2 supplies the amplitude current signal Jt to the resistor 7683, and produces the correction signal K1 at the terminal of the resistor 7683. Therefore, the amplitude current signal Jt and the correction signal K1 change in proportion to the amplitude of the detection signal. The command side creator 7570 has a command unit 7
The output current signal D of 515 is supplied to the transistors 7676, 76
Energize the resistor 7675 via the 77 current mirror,
The command side signal K0 is produced at the terminal of the resistor 7675. That is, the command side signal K0 is generated by converting the output current signal D of the command unit 7515 into a voltage. Therefore, the command side signal K0 is proportional to the output current signal D, and substantially the command unit 7
It corresponds to the output signal of 515. Correction comparator 7580
Applies the correction signal K1 and the command side signal K0 to the transistor 76.
87, 7688, 7689, 7690
The difference current corresponding to the difference between the two is input to the current amplification circuit 7691. The current amplifier 7691 outputs a feedback current signal Ib obtained by amplifying the input current. That is, the correction comparator 758
0 substantially compares the correction signal k1 with the output signal of the command unit 7515, and the feedback current signal Ib corresponding to the comparison result.
Is output.

In this way, the detection signals E1, F1, G
A correction signal K1 that responds to the amplitudes of the three-phase current signals I1, I2, I3 proportional to 1 is created, and a feedback current signal Ib that responds to the comparison result of the correction signal K1 and the command side signal K0 is created.
Transistors 7640-7 in response to the feedback current signal Ib
By changing the output current of the current mirror 649, the three-phase current signals I1, I2, I3 and the three-phase distribution signal M1,
Changing M2 and M3. As a result, a feedback loop for correcting the magnitude of the three-phase current signal and the correction signal in response to the result of comparison between the correction signal and the command side signal is formed. Thereby, the detection signals E1, F1, G of the position detector 7521
Regardless of the amplitude of 1, the amplitudes of the current signals I1, I2, I3 and the distribution signals M1, M2, M3 have a predetermined magnitude corresponding to the command side signal K0. The capacitor 7692 compensates the phase of the feedback loop. Drive unit 75 of FIG.
14 is a first driver 7541, a second driver 7542 and a third driver
A driving signal Va, Vb, Vc obtained by power amplification of the distribution signals M1, M2, M3 of the distribution generator 7531 of the distribution unit 7513, and the three-phase coil 7511A,
Supply to the terminals of 7511B and 7511C.

FIG. 59 shows the first driver 75 of the driving unit 7514.
41, the second driver 7542 and the third driver 7543 are specifically shown. The distribution signal M1 is input to the buffer amplifier 7711 of the first driver 7541, the distribution signal M2 is input to the buffer amplifier 7731 of the second driver 7542, and the distribution signal M3 is input to the buffer amplifier 7751 of the third driver 7543. It Amplifier 7712 of first driver 7541, resistors 7713, 7714, 7715, 771
6 is a buffer amplifier 7711 and a buffer amplifier 775.
The output signal of 1 is taken as a differential signal to obtain the distribution signal M1 and the distribution signal M.
Produces a difference signal of three. Amplifier 7720, resistor 772
1, 7722 power-amplify the output signal of the amplifier 7712 to generate a drive signal Va, and supply the drive signal Va to the power supply terminal of the coil 7511A. Similarly, the amplifier 7732, the resistors 7733, 7734, 7735, 773 of the second driver 7542.
6 is a buffer amplifier 7731 and a buffer amplifier 771
The differential of the output signal of 1 is taken, and the distribution signal M2 and the distribution signal M
Produces a difference signal of one. Amplifier 7740, resistor 774
1, 7742 power-amplifies the output signal of the amplifier 7732 to generate the drive signal Vb, and supplies the drive signal Vb to the power supply terminal of the coil 7511B. Similarly, the amplifier 7752, the resistors 7753, 7754, 7755, 775 of the third driver 7543.
6 is a buffer amplifier 7751 and a buffer amplifier 773
The differential of the output signal of 1 is taken, and the distribution signal M3 and the distribution signal M
Produces a difference signal of two. Amplifier 7760, resistor 776
1, 7762 power-amplifies the output signal of the amplifier 7752 to generate a drive signal Vc, which is supplied to the power supply terminal of the coil 7511C. The amplifiers 7720, 7740, 7
The power supply voltage of + Vm and -Vm is supplied to 760 (+ Vm = 15V, -Vm = -15V).

The drive signals Va, Vb, Vc apply 3-phase drive currents to the 3-phase coils 7511A, 7511B, 7511C, and a driving force in a predetermined direction is generated by electromagnetic action with the field magnet portion 7510. FIG. 63 shows a signal waveform for explaining the operation of this embodiment. Position detecting elements 7630A, 7630A, 730A for detecting the magnetic field of the field portion 7510 as the field portion 7510 rotates (or moves relative to the three-phase coil).
630B and 7630C are sinusoidal detection signals E1-E.
2, F1-F2, G1-G2 are obtained [see FIG. 63 (a): the horizontal axis is the rotational position]. Command signal R of predetermined value [Fig. 63
(B): the vertical axis is the negative side is upward]
The operation of the command current unit 7551, the multiplication command unit 7552, and the command output unit 7553 in FIG. 5 causes the output current signal D of the command unit 7515 to include a harmonic signal component corresponding to the detection signal in a predetermined ratio [Fig. c)]. Since the command side signal K0 is proportional to the output current signal D, the command side signal K0 also contains a harmonic signal component in response to the detection signal in a predetermined ratio.
The distribution generator 7531 and the distribution corrector 7532 have three-phase current signals I1, I2, I3 [FIG. 63 (d)] and three-phase distribution signal M1 that smoothly change in response to the detection signal of the position detector 7521. , M2, M3 are generated, and the correction signal K1 corresponding to the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values [FIG. ] And the correction signal K1 is the command side signal K0
The feedback loop is operated so as to match with. Along with this, the amplitudes of the distribution signals M1, M2, M3 are also corrected in response to the comparison result of the correction signal K1 and the command side signal K0 [FIG. 63 (f)]. As a result, the distribution signals M1, M2, M
The amplitude of 3 has a magnitude in response to the command side signal K0, and is not affected by the amplitude of the detection signal. The first driver 7541, the second driver 7542, and the third driver 7543 of the driver 7514 combine the distribution signals for at least two phases to generate the driving signals Va, Vb, and Vc, thereby generating the driving signal V
Phases a, Vb, and Vc are shifted by about 30 degrees with respect to the distribution signals M1, M2, M3 and the detection signals E1-E2, F1-F2, G1-G2 [FIG. 63 (g)]. In addition, the first driver 7541, the second driver 7542, the third driver 754
3 is a three-phase coil 751 that responds to the distributed signals M1, M2, M3 and power-amplifies the drive signals Va, Vb, Vc.
1A, 7511B, 7511C.

In this embodiment, a correction signal that changes in proportion to the amplitude of the detection signal is created, and the amplitude of the distribution signal is corrected in response to the result of comparison between the correction signal and the command side signal. As a result, the distribution signals M1, M2, M3 and the drive signals Va, V
b and Vc are the position detection elements 763 of the position detector 7521.
0A, 7630B, 7630C variations in sensitivity, magnetic field variations in field portion 7510, and circuit gain variations in distribution generator 7531 are not affected (the influence is extremely small). Further, the distribution generator 7531 and the distribution corrector 7
In 532, a correction signal corresponding to the added value of the unipolar values or the added value of the absolute values of the three-phase current signals is generated,
In response to this correction signal, the amplitude of the distribution signal is corrected. Therefore, the correction signal corresponding to the amplitude of the detection signal can always be obtained with a simple circuit configuration, and accurate correction can be performed.

Further, if necessary, if the configuration such as the command unit of the present embodiment is adopted, an output including a harmonic signal component proportional to the command signal and containing a predetermined proportion of the harmonic signal component responsive to the harmonic signal of the detection signal. Can produce a signal. If a distribution signal corresponding to the comparison result of the command side signal K0 correction signal K1 proportional to this output signal is produced, the distribution signals M1, M2, M3
The drive signals Va, Vb, and Vc can be three-phase sinusoidal signals that smoothly change in response to the detection signal. Therefore, the distortion of the distribution signal and the drive signal is significantly reduced, a uniform generated torque is obtained, and the motor can be smoothly driven. Further, the command unit creates two command current signals in response to the command signal by the command current device, and creates a multiplication command current signal by multiplying one command current signal by the multiplication command device by the harmonic signal of the detection signal, The output device produces an output current signal and a command-side signal by synthesizing the other command current signal and the multiplication command current signal. As a result, the transistors 7914, 7915, 7916 in the multiplication commander are
Can be made to perform a non-linear differential operation, and even if amplitude fluctuations of the detection signal occur, amplitude fluctuations of the multiplication command current signal can be reduced, and the output current signal D and the command side signal K of the command unit can be reduced.
It is possible to reduce variations in the ratio of the harmonic signal components included in 0. In other words, the structure is strong against variations in sensitivity of the position detection element and variations in the magnetic field of the field unit. Further, with the configuration of this embodiment, the position detecting element can be arranged with a high degree of freedom, and by disposing the position detecting element between the salient pole portions of the armature core, the motor structure can be made compact.

Embodiment 14 FIGS. 64 to 66 show the structure of a brushless motor according to Embodiment 14 of the present invention. Also in this embodiment, the mounting positional relationship between the coil and the position detecting element is shifted by an electrical angle of about 30 degrees, and the detecting element is arranged between the coils, so that the small motor can be easily manufactured. FIG. 64 shows an overall configuration diagram. In this embodiment, the distribution generator 8 outputs a switching signal that is phase-shifted by about 30 degrees in electrical angle from the detection signal of the position detecting element.
031, the first driver 80 of the driving unit 7514
41, the second driver 8042, and the third driver 8043 do not perform phase shift. The same parts as those in Example 13 described above are designated by the same reference numerals.

The position detector 75 of the position portion 7512 is shown in FIG.
21 and the specific configuration of the distribution generator 8031 and the distribution corrector 8032 of the distribution unit 7513. Position detector 7521
Position detecting elements 7630A, 7630B, 7630C
Is the position detecting elements 7607a and 7607 of FIG.
b, 7607c, and a voltage is supplied in parallel via a resistor 7631. Differential detection signals E1 and E2 corresponding to the detection magnetic field of the field magnet portion 7510 (corresponding to the permanent magnet 7602 in FIG. 57) are provided at the output terminals of the position detection element 7630A.
Is output and the differential transistor 8 of the distribution generator 8031 is output.
153,8154 base. Differential detection signals F1 and F2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 7630B, and the differential transistor 8
It is supplied to the base of 160,8161. Differential detection signals G1 and G2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 7630C, and the differential transistor 8
167,8168 base. Field part 7
The detection signals E1, F1, G1 change smoothly with the rotational movement of 510, and have an electrical phase difference of 120 degrees.
It is a phase signal.

Transistor 814 of distribution creator 8031
0, 8141, 8142, 8143, 8144, 814
5,8146,8147,8148,8149,815
Reference numerals 0, 8151 and 8152 form a current mirror, and a current value proportional to the feedback current signal Ib flows in. The differential transistors 8153 and 8154 distribute the current value of the transistor 8142 to the collector side in response to the detection signals E1 and E2. The collector current of the transistor 8153 is doubled by the current mirror of the transistors 8155 and 8156, and the current flowing out / in from the connection end of the transistor 8156 and the transistor 8141 is converted into the resistance 817.
4 The collector current of the transistor 8154 is doubled by the current mirror of the transistors 8157, 8158, 8159,
The current flowing out / in from the connection end of the transistor 58 and the transistor 8143 is supplied to the resistor 8175,
The current signal 11 flowing in and out from the connection end of the transistor 8144 is supplied to the distribution corrector 8032. Similarly, the differential transistors 8160 and 8161 distribute the current value of the transistor 8146 to the collector side in response to the detection signals F1 and F2. The collector current of the transistor 8160 is doubled by the current mirror of the transistors 8162 and 8163, and the current flowing out / in from the connection end of the transistor 8163 and the transistor 8145 is supplied to the resistor 8175.

The collector current of the transistor 8161 is doubled by the current mirror of the transistors 8164, 8165, 8166, and the current flowing out / in from the connection end of the transistor 8165 and the transistor 8147 is supplied to the resistor 8176, and the transistor 8166 and the transistor 8166 are connected. The current signal 12 flowing out / in from the connection end of 8148 is supplied to the distribution corrector 8032. Similarly, the differential transistors 8167 and 8168 have detection signals G1 and
In response to G2, the current value of the transistor 8150 is distributed to the collector side. The collector current of the transistor 8167 is doubled by the current mirror of the transistors 8169 and 8170, and the current flowing out / in from the connection end of the transistor 8170 and the transistor 8149 is supplied to the resistor 8176. The collector current of the transistor 8168 is transistor 8171, 8172, 8173.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 8172 and the transistor 8151.
The inflowing current is supplied to the resistor 8174, and the transistor 8
The current signal 13 flowing in and out from the connection end of the transistor 173 and the transistor 8152 is supplied to the distribution corrector 8032.

The distribution signals M1, M2, M3 become three-phase voltage signals that change smoothly in response to the detection signal, and are supplied to the drive unit 7514. Each distribution signal is a signal obtained by synthesizing at least two phases of the detection signal, and is phase-shifted by about 30 degrees with respect to the detection signal. The current signals I1, I2, I3 become three-phase current signals that change smoothly in response to the detection signal, and are supplied to the distribution corrector 8032. The distribution corrector 8032 includes a correction creator 7560 that creates the correction signal K1, a command-side creator 7570 that creates the command-side signal K0, a correction signal K1 and a command-side signal K.
It is composed of a correction comparator 7580 for comparing 0. The correction generator 7560 produces an amplitude current signal Jt that changes in proportion to the amplitude of the detection signal.
1 and a correction output device 7562 for generating a correction signal K1 proportional to the amplitude current signal Jt. The amplitude current generator 7561 is a current acquisition circuit 7695, 7696, to which the three-phase current signals I1, I2, I3 are respectively input.
It is composed of 7697. Current acquisition circuit 769
5, 7696 and 7697 are current signals I1 and I, respectively.
2, a current signal corresponding to the absolute value of I3 or a current signal corresponding to a unipolar value is output. The specific configuration of the current acquisition circuit is similar to that shown in FIG. 48, and detailed description thereof will be omitted.

Current acquisition circuit 769 of amplitude current generator 7561
The output current signals of 5,7696 and 7697 are combined to obtain the amplitude current signal Jt. Since the amplitude current signal Jt is a current signal of the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values, the detection signals E1, F
1, it changes in proportion to the amplitude of G1. Correction output device 756
2 supplies the amplitude current signal Jt to the resistor 7683, and produces the correction signal K1 at the terminal of the resistor 7683. Therefore, the amplitude current signal Jt and the correction signal K1 change in proportion to the amplitude of the detection signal. The command side creator 7570 has a command unit 7
The output current signal D of 515 is supplied to the transistors 7676, 76
Energize the resistor 7675 via the 77 current mirror,
The command side signal K0 is produced at the terminal of the resistor 7675. That is, the command side signal K0 is generated by converting the output current signal D of the command unit 7515 into a voltage. Therefore, the command side signal K0 is proportional to the output current signal D, and substantially the command unit 7
It corresponds to the output signal of 515. Correction comparator 7580
Applies the correction signal K1 and the command side signal K0 to the transistor 76.
87, 7688, 7689, 7690
The difference current corresponding to the difference between the two is input to the current amplification circuit 7691. The current amplifier 7691 outputs a feedback current signal Ib obtained by amplifying the input current. That is, the correction comparator 758
0 substantially compares the correction signal and the output signal of the command unit,
A feedback current signal Ib that responds to the comparison result is output.

In this way, the detection signals E1, F1, G
A correction signal K1 that responds to the amplitudes of the three-phase current signals I1, I2, I3 proportional to 1 is created, and a feedback current signal Ib that responds to the comparison result of the correction signal K1 and the command side signal K0 is created.
Transistors 8140-8 in response to the feedback current signal Ib
The output current of the current mirror 152 is changed to generate three-phase current signals I1, I2, I3 and three-phase distribution signals M1,
The amplitudes of M2 and M3 are changed. As a result, a feedback loop is configured to correct the amplitude of the three-phase distribution signal and the magnitude of the correction signal in response to the comparison result of the correction signal and the command side signal. Accordingly, the detection signal E of the position detector 7521
1, F1, G1 regardless of the amplitude of the current signals I1, I1
2, I3 and the distribution signals M1, M2, M3 have predetermined amplitudes corresponding to the command side signal K0. The capacitor 7692 compensates the phase of the feedback loop. FIG.
The fourth driving unit 7514 includes a first driving unit 8041, a second driving unit 8042, and a third driving unit 8043.
The distribution signals M1, M2, M of the distribution generator 8031 of 513
The drive signals Va, Vb, Vc obtained by power amplification of 3 are supplied to the terminals of the three-phase coils 7511A, 7511B, 7511C.

FIG. 66 shows the first driver 80 of the driving unit 7514.
41, the second driver 8042 and the third driver 8043 are shown. Amplifier 821 of first driver 8041
0, resistors 8211 and 8212 voltage-multiply the distribution signal M1 by a required factor to generate a drive signal Va, and a coil 751
Supply to the power supply terminal of 1A. Similarly, the second driver 804
The second amplifier 8220 and the resistors 8221 and 8222 voltage-amplify the distributed signal M2 by a required number of times to generate the drive signal Vb, and supply the drive signal Vb to the power supply terminal of the coil 7511B. Similarly,
The amplifier 8230 of the third driver 8043, the resistor 8231,
The 8232 voltage-amplifies the distribution signal M3 by a required number of times to generate a drive signal Vc, and supplies the drive signal Vc to the power supply terminal of the coil 7511C. The amplifiers 8210, 8220, and 8230 are supplied with power supply voltages of + Vm and -Vm (+ Vm.
= 15V, -Vm = -15V). Command unit 751 in FIG.
5 is composed of a command current unit 7551, a multiplication command unit 7552, and a command output unit 7553. The specific configuration and operation of these are the same as those shown in FIG. 60, FIG. 61, and FIG. 62 described above, and detailed description thereof will be omitted. The configuration of this embodiment also has the distribution signals M1, M2, M3 and the drive signal V.
a, Vb, and Vc are not affected by the amplitude of the detection signal.
Further, the distribution signals M1, M2, M3 and the drive signal Va,
Vb and Vc smoothly change in a sine wave shape in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly. Further, the position detecting element can be arranged freely, and by disposing it between salient pole portions of the armature core, the motor structure can be made compact.

Embodiment 15 FIGS. 67 to 69 show the structure of a brushless motor according to Embodiment 15 of the present invention. FIG. 67 shows the overall configuration of the fifteenth embodiment. In this embodiment, the distribution generator 8331 and the distribution corrector 8332 generate a correction signal that is proportional to the amplitude of the detection signal of the position detector 7521 and that includes a harmonic signal component of the detection signal, and the correction signal and the command. The amplitude of the distribution signal of the distribution generator 8331 is corrected in response to the result of comparison with the side signal. Further, the mounting positional relationship between the coil and the position detecting element is shifted by an electrical angle of about 30 degrees, and the detecting element is arranged between the coils, so that the small motor can be easily manufactured. The same parts as those in this embodiment described above are designated by the same reference numerals. FIG. 68 shows a specific configuration of the position detector 7521 of the position unit 7512, the distribution generator 8331 and the distribution corrector 8332 of the distribution unit 7513. Position detector 75
21 position detection elements 7630A, 7630B, 7630
C is the position detecting elements 7607a and 760 shown in FIG.
7b and 7607c, and a voltage is supplied in parallel via a resistor 7631. The field detector 7510 (the permanent magnet 7602 of FIG. 57) is connected to the output terminal of the position detection element 7630A.
Corresponding to the detection magnetic field E1
2 is output and supplied to the bases of the differential transistors 8551 and 8452 of the distribution generator 8331. Differential detection signals F1 and F2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 7630B and are supplied to the bases of the differential transistors 8557 and 8558. Differential detection signals G1 and G2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 7630C and are supplied to the bases of the differential transistors 8563 and 8564. The detection signals E1, F1, G1 are accompanied by the rotational movement of the field part 7510.
Changes smoothly and is a three-phase signal having an electrical phase difference of 120 degrees.

Transistor 854 of distribution creator 8331
0,8541,8542,8543,8544,854
5, 8546, 8547, 8548, and 8549 form a current mirror, and a current value proportional to the feedback current signal Ib flows in. The differential transistors 8551 and 8552 are
The current value of the transistor 8542 is distributed to the collector side in response to the detection signals E1 and E2. Transistor 8551
The collector current of the transistor 853 is amplified twice by the current mirror of the transistors 8553 and 8554.
A current flowing out / in from the connection end of the transistor 554 and the transistor 8541 is supplied to the resistor 8571, and the distribution signal M1 is obtained at the terminal of the resistor 8571. The collector current of the transistor 8552 is doubled by the current mirror of the transistors 8555 and 8556, and the collector current of the transistor 855 is amplified.
The current signal I1 flowing out / in from the connection end of the transistor 6 and the transistor 8543 is supplied to the distribution corrector 8332. Similarly, the differential transistors 8557 and 8558 distribute the current value of the transistor 8545 to the collector side in response to the detection signals F1 and F2. The collector current of the transistor 8557 is doubled by the current mirror of the transistors 8559 and 8560,
The current flowing in and out from the connection end of the transistor 8544 is supplied to the resistor 8572, and the distribution signal M2 is obtained at the terminal of the resistor 8572. The collector current of the transistor 8558 is doubled by the current mirror of the transistors 8561 and 8562, and the current signal I2 flowing out / in from the connection end of the transistor 8562 and the transistor 8546 is supplied to the distribution corrector 8332. Similarly,
The differential transistors 8563 and 8564 have detection signals G
In response to 1, G2, the current value of the transistor 8548 is distributed to the collector side. The collector current of the transistor 8563 is doubled by the current mirror of the transistors 8565 and 8566, and the current flowing out and in from the connection end of the transistor 8566 and the transistor 8547 is supplied to the resistor 8573, and the distribution signal M3 is supplied to the terminal of the resistor 8573. It has gained. The collector current of the transistor 8564 is doubled by the current mirror of the transistors 8567 and 8568, and the current signal 1 that flows in and out from the connection end of the transistor 8568 and the transistor 8549.
3 is supplied to the distribution corrector 8332.

The distribution signals M1, M2, M3 become three-phase voltage signals that change smoothly in response to the detection signal and are supplied to the driver 7514. Current signals I1, I2, I3
Becomes a three-phase current signal that smoothly changes in response to the detection signal and is supplied to the distribution corrector 8332. The distribution corrector 8332 is a correction generator 85 that produces the correction signal K1.
10 and the command-side generator 852 that generates the command-side signal K0
0, and a correction comparator 8530 for comparing the correction signal K1 and the command side signal K0. Correction creator 85
Reference numeral 10 denotes an amplitude current generator 8511 that creates two amplitude current signals that change in proportion to the amplitude of the detection signal, and a multiplication correction current signal that creates a harmonic signal that is synchronized with the detection signal and that is multiplied by one of the amplitude current signals. Multiply corrector 851 to create
2 and a correction output device 8513 that outputs a correction signal K1 proportional to the combined correction current signal obtained by combining the other amplitude current signal and the multiplication correction current signal. FIG. 69 shows a specific configuration of the correction generator 8510. Current acquisition circuit 8595, 8596, 8597 of amplitude current meter 8511
Outputs a current signal corresponding to the absolute value of the current signals I1, I2, I3 or a current signal corresponding to the unipolar value, respectively. The specific configuration of the current acquisition circuit is similar to that shown in FIG. 48, and detailed description thereof will be omitted. Current acquisition circuit 8595, 8596, 859 of amplitude current meter 8511
The output current signals of No. 7 are combined to form the amplitude current signal Jt.
The amplitude current signal Jt is a three-phase current signal I1, I2, I3.
Since it is the current signal of the added value of the absolute value of or the added value of the unipolar value, it changes in proportion to the amplitude of the detection signals E1, F1, and G1. Transistors 8598, 8599, 860
The current mirror of 0 is 2 which is proportional to the amplitude current signal Jt.
It outputs two amplitude current signals Jf and Jg.

Transistor 860 of multiplication corrector 8512
2, 8603 distributes the current value of the constant current source 8601 to the collector side in response to the detection signals E1 and E2 of the position detection element, obtains the difference current by the current mirror of the transistors 8604 and 8605, and outputs the transistors 8606 and 860.
7, 8608, 8609, 8610, 8611 and resistor 8
Voltage signal S1 responding to the absolute value of the difference current by 661
Get. That is, the voltage signal S1 that responds to the absolute value of the detection signals E1-E2 is generated. Similarly, the detection signal F1-
A voltage signal S2 responsive to the absolute value of F2 is created in the resistor 8662, and a voltage signal S3 responsive to the absolute value of the detection signals G1-G2 is created in the resistor 8663. Transistor 86
64, 8665, 8666, 8667 and diode 86
68 and 8669 compare the voltage signals S1, S2 and S3 with a predetermined voltage value (including 0V) of the constant voltage source 8675, and shunt the amplitude current signal Jf to each collector side in response to the difference voltage. The collector currents of the transistors 8664, 8665, 8666 are combined to create a combined current, and the combined current and the collector current of the transistor 8667 are compared by the current mirror of the transistors 8671, 8672, and the difference current is reflected in the current mirror of the transistors 8673, 8674. The current value is input, the current value is reduced to about 1/2, and the current value is output as the multiplication correction current signal Qh (inflow current).

The correction output device 8513 is a multiplication correction device 851.
A combined correction current signal is generated by synthesizing the multiplication correction current signal Qh of 2 and the other amplitude current signal Jg of the amplitude current generator 8511. Then, the correction signal K1 is output. Multiplication corrector 8512
The multiplication correction current signal Qh of ## EQU1 ## is responsive to the multiplication result of the voltage signals S1, S2, S3 responsive to the detection signal and the amplitude current signal Jf of the amplitude current device 8511. Transistor 866
With the configuration of 4,8665, 8666, 8667, the multiplication correction current signal Qh changes in response to the multiplication result of the amplitude current signal Jf and the minimum value of the voltage signals S1, S2, S3. The minimum value of the voltage signals S1, S2, S3 that responds to the absolute value of the detection signal is a harmonic signal that is synchronized with the detection signal and that changes six times with respect to a change in one cycle of the detection signal. Therefore, the multiplication correction current signal Qh is a harmonic signal having an amplitude proportional to the amplitude current signal Jf and changing 6 times per cycle of the detection signal. Since the correction signal K1 of the correction output device 8513 is proportional to the combined correction current signal Qh of the multiplication correction current signal Qh and the amplitude current signal Jg, it contains a harmonic signal component that responds to the detection signal in a predetermined ratio.

The command side generator 8520 of FIG. 68 supplies the output current signal d of the command current generator 7050 of the command section 7515 to the resistor 8675 via the current mirrors of the transistors 8676 and 8677, and the terminal of the resistor 8675 is commanded to the command side. Generate signal K0. That is, the command side signal K0 is generated by converting the output current signal d of the command current unit 7050 of the command unit 7515 into a voltage. Therefore, the command side signal K0
Is proportional to the output current signal d, and is substantially the command unit 7515.
It corresponds to the output signal of. The command unit 75 of FIG.
The configuration and operation of the command current unit 7050 of 15 are the same as those shown in FIG. 46 described above, and detailed description thereof will be omitted. The correction comparator 8530 compares the correction signal K1 with the command side signal K0, and inputs the difference current corresponding to the difference between the two to the current amplification circuit 8691. The current amplifier 8691 outputs the feedback current signal Ib obtained by amplifying the input current. That is, the correction comparator 8530 substantially compares the correction signal K1 with the output signal of the command unit 7515, and outputs the feedback current signal Ib responsive to the comparison result.

As a result, the three-phase current signals I1 and I
A correction signal K1 that changes in proportion to the amplitude of the detection signal is generated by 2 and I3, and a feedback current signal Ib that corresponds to the comparison result of the correction signal K1 and the command side signal K0 is generated. Transistors 8540-8549 in response to the feedback current signal Ib
The output current of the current mirror changes, and the three-phase current signals I1, I2, I3 and the three-phase distribution signals M1, M2, M
The amplitude of 3 changes. That is, a feedback loop is configured to correct the amplitude of the three-phase distribution signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the command side signal. As a result, the detection signals E1, E2, F1, of the position detector 7521 are
Regardless of the amplitudes of F2, G1, G2, the current signals I1, I
2, I3 and the distribution signals M1, M2, M3 have predetermined amplitudes corresponding to the command side signal K0. The capacitor 8592 compensates the phase of the feedback loop described above.
At this time, the correction signal K1 of the correction generator 8510 is a voltage signal including a harmonic signal component that responds to the harmonic signal of the detection signal in a predetermined ratio. Since the amplitudes of the distribution signals M1, M2, M3 change in response to the difference between the correction signal K1 and the command side signal K0, the distribution signals M1, M2, M3 have a sine wave shape having an amplitude corresponding to the command side signal K0. Results in a smooth voltage signal.

The first driver 75 of the driving unit 7514 of FIG. 67.
41, the second driver 7542, and the third driver 7543 have the same configurations and operations as those shown in FIG. 59, and detailed description thereof will be omitted. Also in the configuration of this embodiment, the correction signal K that changes in proportion to the amplitude of the detection signal of the position detector
1 is generated, and the amplitudes of the distribution signals M1, M2, M3 are corrected in response to the comparison result of the correction signal K1 and the command side signal K0. As a result, the distribution signals M1, M2, M3 and the drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. Further, in the correction generator 8510 of the distribution corrector 8332, a high frequency signal responsive to the detection signal is obtained, a multiplication correction current signal is generated by multiplying the harmonic signal, and a harmonic signal component responsive to the multiplication correction current signal is predetermined. The correction signal K1 including the ratio is produced. Correction signal K1 and command side signal K
By correcting the amplitudes of the distribution signals M1, M2, M3 in response to the comparison result of 0, it is possible to obtain a distribution signal that smoothly changes in a sinusoidal wave in response to the detection signal. That is, the distribution signals M1, M2, M3 and the drive signal Va,
Vb and Vc smoothly change in a sine wave shape in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly.

Embodiment 16 FIGS. 70 to 72 show the structure of a brushless motor according to Embodiment 16 of the present invention. FIG. 70 shows an overall configuration diagram of the sixteenth embodiment. In the present embodiment, the number of position detecting elements of the position detector is reduced to two in the above-described Embodiment 13 (FIG. 56). As a result, the number of parts in the motor structure portion is reduced, and it becomes easier to manufacture a small motor. The same parts as those in the thirteenth embodiment described above are designated by the same reference numerals. The position detector 8701 of the position part 7512 is shown in FIG.
And distribution generator 8702 and distribution corrector 8 of distribution unit 7513
A specific configuration of 703 is shown. The position detection elements 7630A and 7630B of the position detector 8701 are the three position detection elements 7607a, 7607b and 7607 of FIG.
The voltage is supplied in parallel via a resistor 7631, which corresponds to two of c. That is, the number of position detecting elements attached to the stator is reduced to two. Position detection element 7
Differential detection signals E1 and E2 corresponding to the detection magnetic field of the field magnet portion 7510 (corresponding to the permanent magnet 7602 in FIG. 57) are output to the output terminal of 630A. Similarly, the position detecting element 7
Differential detection signals F1 and F2 corresponding to the detection magnetic field are output to the output terminal of 630B. The detection signals E1 and F1 change smoothly with the rotational movement of the field unit 7510, and E1
And F1 are two-phase signals having an electrical phase difference of 120 degrees. The detection signals E1 and E2 change to opposite phases, and F1 and F2 change to opposite phases. Here, the opposite phase detection signals E2 and F2 are not counted as a new phase number.

Transistor 874 of distribution creator 8702
0,8741, 8742,8743,8744,874
5,8746,8747,8748,8749,875
0 forms a current mirror, and a current value proportional to the feedback current signal Ib flows in. Differential transistors 8751,8
752 distributes the current value of the transistor 8742 to the collector side in response to the detection signals E1 and E2. The collector current of the transistor 8751 is the transistor 8753, 8
The current mirror 754 doubles the current and supplies the current flowing out / in from the connection end of the transistor 8754 and the transistor 8741 to the resistor 8771.
The distribution signal M1 is obtained at the terminal 71. Transistor 8
The collector current of 752 is transistor 8755,875.
A current signal I1 which is amplified and doubled by the current mirror 6 and flows out / in from the connection end of the transistor 8756 and the transistor 8743 is supplied to the distribution corrector 8703. Similarly, differential transistors 8757 and 8758
Is a transistor 874 in response to the detection signals F1 and F2.
The current value of 5 is distributed to the collector side. Transistor 87
The collector current of 57 is transistors 8759 and 8760.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 8760 and the transistor 8744.
The inflowing current is supplied to the resistor 8772, and the distribution signal M2 is obtained at the terminal of the resistor 8772.

The collector current of the transistor 8758 is doubled by the current mirror of the transistors 8761 and 8762, and the current signal I2 flowing out / in from the connection end of the transistor 8762 and the transistor 8746 is supplied to the distribution corrector 8703. The differential transistors 8763 and 8764 distribute the current value of the transistor 8748 to the collector side in response to the detection signals E1 and E2,
The differential transistors 8765 and 8766 use the detection signal F
In response to 1, F2, the current value of the transistor 8749 is distributed to the collector side. The collector current of the transistor 8764 and the collector current of the transistor 8766 are combined and amplified twice by the current mirror of the transistors 8767 and 8768, and the current flowing out / in from the connection end of the transistor 8768 and the transistor 8747 is supplied to the resistor 8773. Distribution signal M to the terminal of resistor 8773
I got 3. The collector current of the transistor 8763 and the collector current of the transistor 8765 are combined, amplified twice by the current mirror of the transistors 8769 and 8770, and the current signal I3 flowing out / in from the connecting end of the transistor 8770 and the transistor 8750 is distributed and corrected by the compensator 8703. Is being supplied to. Thus, 2
The phase detection signals E1 and F1 are arithmetically combined to generate a 3-phase signal.

The distributed signals M1, M2, M3 change smoothly in response to the two-phase detection signals, and are electrically substantially 12
It becomes a three-phase voltage signal having a phase difference of 0 degree, and the driving unit 7
514. The current signals I1, I2, I3 are 2
It smoothly changes in response to the phase detection signal, and becomes a three-phase current signal having an electrical phase difference of substantially 120 degrees,
It is supplied to the distribution corrector 8703. Distribution corrector 8703
Is a correction generator 7560 for generating the correction signal K1, a command side generator 7570 for generating the command side signal K0, and a correction comparator 758 for comparing the correction signal K1 and the command side signal K0.
It is composed of 0s. The correction generator 7560 includes an amplitude current generator 7561 that produces an amplitude current signal that changes in proportion to the amplitude of the detection signal, and a correction output device 7562 that outputs a correction signal K1 that is proportional to the amplitude current signal. These specific configurations are the same as those shown in the distribution compensator 7532 in FIG. 58, and detailed description will be omitted. The distribution generator 8702 and the distribution corrector 8703 use three-phase detection signals to generate three-phase current signals I1 and I2.
2, I3 are generated, the correction signal K1 that changes in proportion to the amplitude of the detection signal is generated, and the correction signal K1 and the command side signal K0 are generated.
A feedback current signal Ib is produced in response to the result of the comparison. Transistor 8740 in response to feedback current signal Ib
.About.8750 current mirror output current changes, three-phase current signals I1, I2, I3 and three-phase distribution signal M
The amplitudes of 1, M2 and M3 change. That is, a feedback loop is configured to correct the amplitude of the three-phase distribution signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the command side signal. As a result, regardless of the amplitudes of the two-phase detection signals E1, E2, F1, F2 of the position detector 8701, the current signal I
The amplitudes of 1, I2, I3 and the distribution signals M1, M2, M3 have a required magnitude corresponding to the command side signal K0.

The command unit 7515 shown in FIG.
551, multiplication command device 8705, and command output device 7553. The command current unit 7551 and the command output unit 7553 are the same as those shown in FIGS. 60 and 62, respectively, and detailed description thereof will be omitted. FIG. 72 shows a specific configuration of the multiplication command unit 8705. The transistors 8802 and 8803 of the multiplication commander 8705 distribute the current value of the constant current source 8801 to the collector side in response to the detection signals E1 and E2 of the position detection element, and the transistors 8804 and 8805.
The differential current is obtained by the current mirror of the transistors 8806, 8807, 8808, 8809, 8810,
The voltage signal S1 corresponding to the absolute value of the difference current is obtained by 8811 and the resistor 8861. That is, the detection signals E1-E
A voltage signal S1 responsive to an absolute value of 2 is produced. Similarly, a constant current source 8821 and transistors 8822 to 883 are provided.
1, the resistor 8862 produces a voltage signal S2 in response to the absolute value of the detection signals F1-F2 at the terminal of the resistor 8862.

The transistors 8842 and 8843 distribute the current of the constant current source 8841 to the collector side in response to the detection signals E1 and E2, and the transistors 8845 and 8846 respond to the detection signals F1 and F2 and the current of the constant current source 8844. Is distributed to the collector side. The combined current of the collector current of the transistor 8843 and the collector current of the transistor 8846 is compared with the combined current of the collector current of the transistor 8842 and the collector current of the transistor 8845 by the current mirror of the transistors 8847 and 8848 to obtain the difference current. Transistors 8849, 88
50,8851,8852,8853,8854 and resistor 8863 create a voltage signal S3 in response to the absolute value of the difference current. That is, from the two-phase detection signal, 3
A signal of the third phase is generated, and a voltage signal S3 that responds to the absolute value of the signal of the third phase is generated. Transistor 886
4,8865,8866,8867 and diode 886
8, 8869 compares the voltage signals S1, S2, S3 with a predetermined voltage value (including 0V) of the constant voltage source 8875, and outputs the second command current signal P2 of the command current generator 7551 in response to the difference voltage. Divide into each collector side. Transistor 886
The collector currents of 4,8865 and 8866 are combined to create a combined current, and the combined current and the transistor 886 are combined by the current mirror of the transistors 8871 and 8872.
7 is compared, and the difference current is input to the current mirrors of the transistors 8873 and 8874, the current value is reduced to about 1/2, and the multiplication command current signal Q
It is output as (inflow current).

Multiplication command current signal Q of multiplication command unit 8705
In response to the multiplication result of the voltage signals S1, S2, S3 responsive to the detection signal and the second command current signal P2 of the command current generator 7551. Transistors 8864, 8865, 8
With the configuration of 866 and 8867, the voltage signals S1, S2 and
The multiplication command current signal Q changes in response to the multiplication result of the minimum value of S3 and the command current signal P2. The minimum value of the voltage signals S1, S2, S3 that responds to the absolute value of the detection signal is a harmonic signal that is synchronized with the detection signal and that changes six times with respect to a change in one cycle of the detection signal. Therefore, the multiplication command current signal Q is
The harmonic signal has an amplitude proportional to the command current signal P2 and changes 6 times per cycle of the detection signal. The output current signal D of the command output device 7553 is proportional to the combined command current signal Q of the multiplication command current signal Q and the first command current signal P1, and therefore contains a harmonic signal component in response to the detection signal in a predetermined ratio. The command-side signal K0 of the command-side creator 7570 is proportional to the output current signal D of the command unit 7515, and therefore becomes a signal containing a harmonic signal component that responds to the harmonic signal of the detection signal in a predetermined ratio. This command side signal K0 and the correction signal K
Since the amplitude of the distribution signal is corrected according to the comparison result of 1, the distribution signals M1, M2, M3 are sinusoidal smooth three-phase voltage signals.

The first driver 75 of the driving unit 7514 of FIG. 70.
41, the second driver 7542, and the third driver 7543 have the same configurations and operations as those shown in FIG. 59, and detailed description thereof will be omitted. As a result, the distribution signal M
It is possible to obtain smooth sinusoidal wave-shaped three-phase drive signals Va, Vb, Vc in response to 1, M2, M3. In the configuration of the present embodiment, the drive signals for the three-phase coils are produced using the two-phase detection signals of the position detector. As a result, the number of position detecting elements may be small, and the motor configuration becomes extremely simple. Further, the correction signal K1 that changes in proportion to the amplitudes of the two-phase detection signals of the position detector is generated, and the correction signal K1 is generated.
1 and the distribution signal M in response to the comparison result of the command side signal K0
The amplitudes of 1, M2 and M3 are corrected. As a result, the distribution signals M1, M2, M3 and the drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal. In addition, a multiplication command device is provided in the command unit to obtain a high frequency signal that responds to the two-phase detection signals, to generate a multiplication command current signal that is multiplied by a harmonic signal, and a harmonic signal component that responds to the multiplication command current signal. Output current signal D and command side signal K of the command section including a predetermined ratio
It produces 0. As a result, the distribution signals M1 and M
2, M3 and the drive signals Va, Vb, Vc smoothly change in a sine wave shape in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly.

Embodiment 17 FIGS. 73 to 75 show the structure of a brushless motor according to Embodiment 17 of the present invention. FIG. 73 shows an overall configuration diagram of the seventeenth embodiment. In this embodiment, the number of position detecting elements of the position detector is reduced to two in the above-described fifteenth embodiment (FIG. 67). As a result, the number of parts in the motor structure portion is reduced, and it becomes easier to manufacture a small motor. The same parts as those in Example 15 described above are designated by the same reference numerals. In FIG. 73, the position detector 8701 of the position unit 7512, the distribution generator 8902 and the distribution corrector 890 of the distribution unit 7513 are shown.
3 shows a specific configuration. The position detection elements 7630A and 7630B of the position detector 8701 correspond to two of the three position detection elements 7607a, 7607b and 7607c of FIG. There is. A field portion 7510 (corresponding to the permanent magnet 7602 in FIG. 57) is provided at the output terminal of the position detection element 7630A.
The differential detection signals E1 and E2 corresponding to the detection magnetic field are output. Similarly, differential detection signals F1 and F2 corresponding to the detection magnetic field are output to the output terminal of the position detection element 7630B. The detection signal E is generated in accordance with the rotational movement of the field part 7510.
1, F1 changes smoothly, and E1 and F1 are electrically 12
It is a two-phase signal having a phase difference of 0 degree.

Transistor 894 of distribution creator 8902
0,8941, 8942, 8943, 8944, 894
5,8946,8947,8948,8949,895
0 forms a current mirror, and a current value proportional to the feedback current signal Ib flows in. Differential transistors 8951,8
952 distributes the current value of the transistor 8942 to the collector side in response to the detection signals E1 and E2. The collector current of the transistor 8951 is the transistor 8953, 8
The current mirror 954 doubles the current, and the current flowing out / in from the connection end of the transistor 8954 and the transistor 8941 is supplied to the resistor 8971.
The distribution signal M1 is obtained at the terminal 71. Transistor 8
The collector current of 952 is the transistors 8955 and 895.
A current signal 11 which is amplified twice by the current mirror 6 and flows in and out from the connection end of the transistor 8956 and the transistor 8943 is supplied to the distribution corrector 8903. Similarly, differential transistors 8957 and 8958
Is a transistor 894 in response to the detection signals F1 and F2.
The current value of 5 is distributed to the collector side. Transistor 89
The collector current of 57 is transistors 8959 and 8960.
Is amplified twice by the current mirror of and flows out from the connection end of the transistor 8960 and the transistor 8944.
The inflowing current is supplied to the resistor 8972, and the distribution signal M2 is obtained at the terminal of the resistor 8972.

The collector current of the transistor 8958 is doubled by the current mirror of the transistors 8961 and 8962, and the current signal 12 flowing out / in from the connection end of the transistor 8962 and the transistor 8946 is supplied to the distribution corrector 8903. The differential transistors 8963 and 8964 distribute the current value of the transistor 8948 to the collector side in response to the detection signals E1 and E2,
The differential transistors 8965 and 8966 have a detection signal F.
In response to 1, F2, the current value of the transistor 8949 is distributed to the collector side. The collector current of the transistor 8964 and the collector current of the transistor 8966 are combined and amplified twice by the current mirror of the transistors 8967 and 8968, and the current flowing out / in from the connection end of the transistor 8968 and the transistor 8947 is supplied to the resistor 8973. Distribution signal M to the terminal of resistor 8973
I got 3. The collector current of the transistor 8963 and the collector current of the transistor 8965 are combined, amplified twice by the current mirror of the transistors 8969 and 8970, and the current signal I3 flowing out / in from the connection end of the transistor 8970 and the transistor 8950 is distributed and corrected by the compensator 8903. Is being supplied to. Thus, 2
The phase detection signals E1 and F1 are arithmetically combined to generate a 3-phase signal.

The distributed signals M1, M2, M3 change smoothly in response to the two-phase detection signals, and are electrically substantially 12
It becomes a three-phase voltage signal having a phase difference of 0 degree, and the driving unit 7
514. The current signals I1, I2, I3 are 2
It smoothly changes in response to the phase detection signal, and becomes a three-phase current signal having an electrical phase difference of substantially 120 degrees,
It is supplied to the distribution corrector 8903. Distribution corrector 8903
Is a correction generator 8905 that generates the correction signal K1, a command-side generator 8520 that generates the command-side signal K0, and a correction comparator 853 that compares the correction signal K1 and the command-side signal K0.
It is composed of 0s. The correction generator 8905 includes an amplitude current generator 8511 that creates two amplitude current signals that change in proportion to the amplitude of the detection signal, and a multiplication correction that creates a harmonic signal synchronized with the detection signal and multiplies it by one of the amplitude current signals. It is composed of a multiplication corrector 8906 that produces a current signal and a correction output device 8513 that outputs a correction signal K1 that is proportional to the combined correction current signal obtained by combining the other amplitude current signal and the multiplied correction current signal. FIG. 75 shows a specific configuration of the correction generator 8905. The current acquisition circuits 8595, 8596, 8597 of the amplitude current device 8511 output the current signal corresponding to the absolute value of the current signals 11, 12, 13 or the current signal corresponding to the unipolar value, respectively. The specific configuration of the current acquisition circuit is similar to that shown in FIG. 48, and detailed description thereof will be omitted. Amplitude ammeter 8511
The output current signals of the current acquisition circuits 8595, 8596 and 8597 are combined to form an amplitude current signal Jt. Since the amplitude current signal Jt is a current signal of the added value of the absolute values of the three-phase current signals I1, I2, I3 or the added value of the unipolar values, it changes in proportion to the amplitude of the detection signals E1, F1. The current mirror of the transistors 8598, 8599, 8600 outputs two amplitude current signals Jf, Jg proportional to the amplitude current signal Jt.

Transistor 900 of Multiply Corrector 8906
2, 9003 distribute the current value of the constant current source 9001 to the collector side in response to the detection signals E1 and E2 of the position detecting element, and obtain the difference current by the current mirror of the transistors 9004 and 9005.
7, 9008, 9009, 9010, 9011 and resistor 9
The voltage signal S1 that responds to the absolute value of the difference current by 061
Get. That is, the voltage signal S1 that responds to the absolute value of the detection signals E1-E2 is generated. Similarly, the constant current source 502
The voltage signal S2 corresponding to the absolute value of the detection signals F1-F2 is generated at the terminal of the resistor 9062 by the first transistor 9022 to 9031 and the resistor 9062. The transistors 9042 and 9043 distribute the current of the constant current source 9041 to the collector side in response to the detection signals E1 and E2, and the transistors 9045 and 9046 respond to the detection signals F1 and F2 and the current of the constant current source 9044 to the collector side. Distribute to. Collector current of transistor 9043 and transistor 90
The combined current of the collector current of 46 is the transistor 904.
The current mirror of 7, 9048 compares the collector current of the transistor 9042 with the combined current of the collector current of the transistor 9045 to obtain the difference current.
Transistors 9049, 9050, 9051, 905
2, 9053, 9054 and the resistor 9063 generate a voltage signal S3 in response to the absolute value of the difference current. That is, the signal of the third phase is generated from the detection signal of the two phases,
A voltage signal S3 that responds to the absolute value of the signal of the third phase is created.

Transistors 9064, 9065, 906
6, 9067 and the diodes 9068, 9069 compare the voltage signals S1, S2, S3 with a predetermined voltage value (including 0 V) of the constant voltage source 9075, and respond to the difference voltage between them to generate the amplitude current signal of the amplitude current meter 8511. Divide Jf to each collector side. The collector currents of the transistors 9064, 9065 and 9066 are combined to produce a combined current, and the combined current and the collector current of the transistor 9067 are compared by the current mirror of the transistors 9071 and 9072.
The difference current is input to the current mirrors of the transistors 9073 and 9074, the current value thereof is reduced to about 1/2, and the multiplication correction current signal Qh (inflow current) is output.

The correction output device 8513 is a multiplication correction device 890.
The combined correction current signal Qh of 6 and the other amplitude current signal Jg of the amplitude current device 8511 are combined to generate a combined correction current signal, and the combined correction current signal is supplied to the resistor 8691 through the current mirrors of the transistors 8681 and 8682.
The correction signal K1 is output from the terminal of the resistor 8691. The multiplication correction current signal Qh of the multiplication corrector 8906 is responsive to the multiplication result of the voltage signals S1, S2, S3 responsive to the two-phase detection signals and the correction current signal Jf of the amplitude rectifier 8511. Transistors 9064, 9065, 9066, 90
With the configuration of 67, the multiplication correction current signal Qh changes in response to the multiplication result of the amplitude current signal Jf and the minimum value of the voltage signals S1, S2, S3. The minimum value of the voltage signals S1, S2, S3 responsive to the absolute value of the detection signal is synchronized with the detection signal,
It is a harmonic signal that changes six times with respect to one cycle of the detection signal. Therefore, the multiplication correction current signal Qh is a harmonic signal having an amplitude proportional to the amplitude current signal Jf and changing 6 times per cycle of the detection signal. Correction output device 8513
The correction signal K1 is proportional to the combined correction current signal Qh of the multiplication correction current signal Qh and the amplitude current signal Jg, and contains a harmonic signal component that responds to the detection signal in a predetermined ratio.

The command-side generator 8520 in FIG. 74 produces a command-side signal K0 obtained by converting the output current signal d of the command current generator 7050 of the command unit 7515 into a voltage. Therefore,
The command side signal K0 is proportional to the output current signal d, and substantially corresponds to the output signal of the command unit 7515. The correction comparator 8530 compares the correction signal K1 with the command side signal K0,
The feedback current signal Ib is output in response to the difference between the two. That is, the correction comparator 8530 uses the correction signal K1 and the command unit 7
The output signals of 515 are substantially compared, and the feedback current signal Ib corresponding to the comparison result is output. Command generator 85
The specific configurations of 20 and the correction comparator 8530 are the same as those shown in FIG. 68, and detailed description thereof will be omitted.
The configuration and operation of the command current unit 7050 of the command unit 7515 of FIG. 73 are the same as those shown in FIG. 46 described above, and detailed description thereof will be omitted. As a result, the correction signal K1 that changes in proportion to the amplitude of the two-phase detection signal is generated by the three-phase current signals I1, I2, I3, and the correction signal K1.
And the feedback current signal Ib in response to the comparison result of the predetermined signal K0
Is made. The output currents of the current mirrors of the transistors 8940 to 8950 change in response to the feedback current signal Ib, and the amplitudes of the three-phase current signals I1, I2, I3 and the three-phase distribution signals M1, M2, M3 change. That is, a feedback loop is configured to correct the amplitude of the three-phase distribution signal and the magnitude of the correction signal in response to the result of comparison between the correction signal and the command side signal. As a result, the amplitudes of the current signals I1, I2, I3 and the distribution signals M1, M2, M3 correspond to the command side signal K0 regardless of the amplitudes of the two-phase detection signals E1, E2, F1, F2 of the position detector 8701. It will be the required size. At this time, the correction signal K1 of the correction generator 8905 is a voltage signal containing a harmonic signal component that responds to the harmonic signal of the detection signal in a predetermined ratio. The correction signal K1 and the command side signal K
Since the amplitudes of the distributed signals M1, M2, M3 change in response to the comparison result of 0, the distributed signals M1, M2, M3 are smooth sinusoidal voltage signals having the amplitude corresponding to the command side signal K0. .

The first driver 75 of the driving unit 7514 of FIG. 73.
41, the second driver 7542, and the third driver 7543 have the same configurations and operations as those shown in FIG. 59, and detailed description thereof will be omitted. As a result, the distribution signal M
It is possible to obtain smooth sinusoidal wave-shaped three-phase drive signals Va, Vb, Vc in response to 1, M2, M3. In the configuration of the present embodiment, the drive signals for the three-phase coils are produced using the two-phase detection signals of the position detector. As a result, the number of position detecting elements may be small, and the motor configuration becomes extremely simple. Further, the correction signal K1 that changes in proportion to the amplitudes of the two-phase detection signals of the position detector is generated, and the correction signal K1 is generated.
1 and the distribution signal M in response to the comparison result of the command side signal K0
The amplitudes of 1, M2 and M3 are corrected. As a result, the distribution signals M1, M2, M3 and the drive signals Va, Vb, Vc are not affected by the amplitude of the detection signal.

The correction generator 8 of the distribution corrector 8903.
A multiplying corrector 8906 is provided in 905 to obtain a high frequency signal that responds to the two-phase detection signals, create a multiplying correction current signal by multiplying the harmonic signal, and determine a harmonic signal component that responds to the multiplying correction current signal. The correction signal K1 including the ratio is produced. As a result, the distribution signals M1, M2, M3 and the drive signals Va, Vb, Vc smoothly change in a sine wave shape in response to the detection signal. Therefore, it is possible to obtain a distribution signal and a drive signal with less distortion, obtain a uniform generated torque, and drive the motor smoothly.

Embodiment 18 FIGS. 76 to 77 show the structure of a brushless motor according to Embodiment 18 of the present invention. In the eighteenth embodiment, the above-described first embodiment is used.
4 (FIG. 64), the first driver 9 of the driver 7514
The configuration of 301, the second driver 9302, and the third driver 9303 is PWM drive (pulse width modulation drive), and the drive unit 7
Power saving of 514 is aimed at. In addition, the first embodiment described above
The same parts as those shown in FIG. 4 have the same numbers. FIG. 77 shows specific configurations of the first driver 9301, the second driver 9302, and the third driver 9303 of the driver 7514. The comparator 9321 of the first driver 9301 compares the triangular wave signal Nt generated by the triangular wave generation circuit 9310 with the distribution signal M1 to generate the PWM signal W1 having a pulse width corresponding to the distribution signal M1. In response to the level of the PWM signal W1, the drive transistors 9322 and 9323 are complementarily turned on / off to drive the drive transistor 932.
2, 9323 and drive diodes 9324 and 9325 supply a drive signal Va that digitally changes in response to the PWM signal W1 to the power supply terminal of the coil 7511A.
Similarly, the comparator 9331 of the second driver 9302
Is the triangular wave signal Nt generated by the triangular wave generation circuit 9310.
Is compared with the distribution signal M2 to generate a PWM signal W2 having a pulse width corresponding to the distribution signal M2. The drive transistors 9332 and 9333 are responsive to the level of the PWM signal W2.
Are turned on and off in a complementary manner, and drive transistor 9
332, 9333 and drive diodes 9334, 9335
Thus, the drive signal Vb that digitally changes in response to the PWM signal W2 is supplied to the power supply terminal of the coil 7511B. Similarly, the comparator 934 of the third driver 9303
1 is a triangular wave signal N generated by the triangular wave generation circuit 9310.
By comparing t with the distribution signal M3, a PWM signal W3 having a pulse width corresponding to the distribution signal M3 is generated. PWM signal W3
Driving transistors 9342 and 934 in response to the level of
3 are complementarily turned on / off to drive the transistors 9342 and 9343 and the driving diodes 9344 and 934.
5, the drive signal Vc that changes digitally in response to the PWM signal W3 is supplied to the power supply terminal of the coil 7511C.

Position portion 7512 and distribution portion 7513 of FIG. 76.
The configuration and operation of the command unit 7515 and the command unit 7515 are the same as those in the first embodiment described above.
4 is the same as that of No. 4 and detailed description thereof will be omitted. In this embodiment, the first driver 9301, the second driver 9302, and the third driver 9303 of the driving unit 7512 are distributed signals M1 and M.
P in which PWM operation is performed in response to 2, M3 and power is amplified
The WM drive signals Va, Vb, Vc are supplied to the three-phase coil 7511.
A, 7511B, 7511C. This allows
While supplying sufficient drive power to the three-phase coil, power loss in the drive unit 7514 is significantly reduced. That is, the power loss in the drive transistor and the drive diode is significantly reduced. As a result, a brushless motor with high power efficiency is obtained. In addition, the first driver 9301, the second driver 9302, and the third driver 9303 shown in this embodiment.
The configuration of can be applied to the driver of each of the above embodiments,
The power loss in each embodiment can be reduced.

Various modifications can be made to the specific configurations of the above-described embodiments. The coil of each phase may be configured by connecting a plurality of coils in series or in parallel. Each coil may be a concentrated winding, a distributed winding, or an air core coil without a salient pole portion. The three-phase coil is not limited to star connection, but may be delta connection. The position detection element is not limited to the hall element or the magnetoelectric conversion element. Various changes can be made to the relative relationship between the coil and the position detecting element. The phase shift performed as necessary is not limited to one of the distributor and the switching generator, but may be shared by both. The structure of the motor structure is not limited to the case where the field magnet portion has a plurality of magnetic pole portions (not limited to four poles), and the field magnetic flux generated by the permanent magnet is linked to the coil. It suffices that the interlinkage magnetic flux to the coil changes with the relative movement of the coil. For example, a structure may be adopted in which a bias magnetic field is applied by a permanent magnet, and the tooth portion on the field side and the tooth portion at the tip of the salient pole wound with the coil face each other while rotating or moving. Further, the brushless motor is not limited to the rotary type, but may be a linear type brushless motor in which a magnetic field portion or a coil moves linearly.

In the switching generator and the switching corrector,
A feedback loop is formed so that the amplitude of the switching signal can be accurately matched with the required value corresponding to the predetermined signal. In the above-described embodiment, the current feedback signal is used, but the present invention is not limited to such a case, and for example, a voltage feedback signal may be used to change the voltage supplied to the position detection element. Further, the configuration of the feedback loop is not limited, and for example, the amplitude of the switching signal may be feed-forward corrected in response to the result of comparison between the correction signal and the predetermined signal. In addition, in the distribution generator and the distribution compensator, a feedback loop is configured so that the amplitude of the distribution signal accurately matches the required value corresponding to the command side signal. In the above-described embodiment, the current feedback signal is used, but the present invention is not limited to such a case, and for example, a voltage feedback signal may be used to change the voltage supplied to the position detection element. Further, the configuration of the feedback loop is not limited, and for example, the amplitude of the distribution signal may be feed-forward corrected in response to the result of comparison between the correction signal and the command side signal. In the above-described embodiment, the command-side creator is included in the distribution corrector, but the present invention is not limited to such a case, and the command-side creator may be included in the command unit. It goes without saying that it is included in the invention. Further, in the above-described embodiment, the correction signal that changes in proportion to the detection signal of the position detector is simply created as the added value of the absolute values of the three-phase current signals or the added value of the unipolar values. Is not limited to such cases. Further, each driver of the driving unit may have any configuration as long as it has a configuration in which the distributed signal is power-amplified and supplied to the three-phase coil. Other,
It goes without saying that various modifications are possible without changing the gist of the present invention and are included in the present invention.

[0173]

As described above, according to the first type of invention of the brushless motor of the present invention, the correction signal which changes in proportion to the detection signal of the position detector is produced, and the correction signal is compared with the predetermined signal. Correct the output signal amplitude of the switching generator,
A three-phase distribution signal is produced in response to the result of multiplication of the output signal of the command section and the output signal of the switching generator, and a drive signal obtained by power-amplifying this distribution signal is supplied to the three-phase coil. Therefore, the influence of the sensitivity variation of the position detection element and the gain variation of the processing circuit is significantly reduced, and the fluctuation of the drive gain of the brushless motor during mass production is significantly reduced. Also,
In the second type invention of the brushless motor of the present invention,
A switching generator is created by generating a correction signal that changes in accordance with the addition value of the unipolar values or the addition value of the absolute values of the three-phase current signals in response to the detection signal of the position detector, and comparing the correction signal with a predetermined signal. The amplitude of the output signal of is corrected, a three-phase distribution signal is produced in response to the multiplication result of the output signal of the command section and the output signal of the switching generator, and the drive signal obtained by power-amplifying this distribution signal is supplied to the three-phase coil. We are supplying. Therefore, the influence of the sensitivity variation of the position detection element and the gain variation of the processing circuit is significantly reduced, and the fluctuation of the drive gain of the brushless motor during mass production is significantly reduced.

Further, in the third type invention of the brushless motor of the present invention, a correction signal which changes in proportion to the amplitude of the detection signal of the position detector is produced, and the correction signal and the output signal of the command section are compared. The amplitude of the distribution signal is corrected, and the drive signal obtained by power-amplifying the distribution signal is supplied to the three-phase coils. Therefore, the influence of the sensitivity variation of the position detection element and the gain variation of the processing circuit is significantly reduced, and the fluctuation of the drive gain of the brushless motor during mass production is significantly reduced. Further, in the fourth type invention of the brushless motor of the present invention, the correction that changes corresponding to the added value of the unipolar values or the added value of the absolute values of the three-phase current signals in response to the detection signal of the position detector A signal is generated, the correction signal is compared with the output signal of the command unit to correct the amplitude of the distribution signal, and the drive signal obtained by power-amplifying the distribution signal is supplied to the three-phase coils. Therefore, the influence of the sensitivity variation of the position detection element and the gain variation of the processing circuit is significantly reduced, and the fluctuation of the drive gain of the brushless motor during mass production is significantly reduced. Further, in many types of inventions of the brushless motor of the present invention, the distribution signal and the driving signal are devised so as to have a smooth sinusoidal waveform with less distortion in response to the detection signal, and the fluctuation of the driving force is made extremely small. ing.

[Brief description of the drawings]

FIG. 1 is a diagram showing an overall configuration according to a first embodiment of the present invention.

FIG. 2 is a diagram showing a motor structure in the first embodiment.

FIG. 3 is a diagram showing a circuit configuration of a command current generator 4050 according to the first embodiment.

FIG. 4 is a diagram showing a circuit configuration of a position detector 4021, a switching generator 4022, and a switching corrector 4023 in the first embodiment.

FIG. 5 is a diagram showing a circuit configuration of a current acquisition circuit 4195 according to the first embodiment.

FIG. 6 is a diagram showing a circuit configuration of a distributor 4031 according to the first embodiment.

FIG. 7 is a diagram showing a circuit configuration of a first driver 4041, a second driver 4042, and a third driver 4043 in the first embodiment.

FIG. 8 is a diagram showing signal waveforms in the first embodiment.

FIG. 9 is a diagram showing an overall configuration according to a second embodiment of the present invention.

FIG. 10 is a diagram showing a circuit configuration of a command current generator 4301 according to a second embodiment.

FIG. 11 is a diagram illustrating a circuit configuration of a multiplication commander 4302 according to the second embodiment.

FIG. 12 is a diagram showing a circuit configuration of a command output device 4303 in the second embodiment.

FIG. 13 is a diagram showing a signal waveform according to the second embodiment.

FIG. 14 is a diagram showing an overall configuration according to a third embodiment of the present invention.

FIG. 15 is a diagram showing a motor structure according to a third embodiment.

FIG. 16 is a diagram showing a circuit configuration of a position detector 4521, a switching generator 4522, and a switching corrector 4523 in the third embodiment.

FIG. 17 is a diagram showing a circuit configuration of a distributor 4531 in the third embodiment.

FIG. 18 illustrates a first driver 4541 and a second driver according to the third embodiment.
It is a figure which shows the circuit structure of the driver 4542 and the 3rd driver 4543.

FIG. 19 is a diagram showing a circuit configuration of a command current generator 4551 according to the third embodiment.

FIG. 20 is a diagram showing a circuit configuration of a multiplication command unit 4552 according to the third embodiment.

FIG. 21 is a diagram showing a circuit configuration of a command output device 4553 in the third embodiment.

FIG. 22 is a diagram showing a signal waveform according to the third embodiment.

FIG. 23 is a diagram showing an overall configuration according to a fourth embodiment of the present invention.

FIG. 24 is a diagram showing a circuit configuration of a position detector 4521, a switching generator 5022, and a switching corrector 5023 in the fourth embodiment.

FIG. 25 is a diagram showing a circuit configuration of a distributor 5031 in the fourth embodiment.

FIG. 26 is a diagram showing a circuit configuration of a command output device 5053 in the fourth embodiment.

FIG. 27 is a diagram showing an overall configuration according to a fifth embodiment of the present invention.

FIG. 28 is a diagram illustrating a circuit configuration of a position detector 4521, a switching generator 5302, and a switching corrector 5303 according to the fifth embodiment.

FIG. 29 is a diagram illustrating a circuit configuration of a setting generator 5320 according to the fifth embodiment.

FIG. 30 is a diagram showing an overall configuration according to a sixth embodiment of the present invention.

FIG. 31 is a diagram showing a circuit configuration of a position detector 4521, a switching generator 5502, and a switching corrector 5503 according to the sixth embodiment.

FIG. 32 is a diagram illustrating a circuit configuration of a correction generator 5510 according to the sixth embodiment.

FIG. 33 is a diagram showing an overall configuration according to a seventh embodiment of the present invention.

FIG. 34 is a diagram showing a circuit configuration of a position detector 5701, a switching generator 5702, and a switching corrector 5703 in the seventh embodiment.

FIG. 35 is a diagram showing a circuit configuration of a multiplication command unit 5705 according to the seventh embodiment.

FIG. 36 is a diagram showing the overall structure of an eighth embodiment of the present invention.

FIG. 37 is a diagram showing a circuit configuration of a position detector 5701, a switching generator 5902, and a switching corrector 5903 in the eighth embodiment.

FIG. 38 is a diagram showing a circuit configuration of a setting generator 5905 according to the eighth embodiment.

FIG. 39 is a diagram showing an overall configuration according to a ninth embodiment of the present invention.

FIG. 40 is a diagram showing a circuit configuration of a position detector 5701, a switching generator 6102, and a switching corrector 6103 in the ninth embodiment.

FIG. 41 is a diagram showing a circuit configuration of a correction generator 6105 in the ninth embodiment.

FIG. 42 is a diagram showing an overall structure of a tenth embodiment of the present invention.

43 is a diagram showing a circuit configuration of a first driver 6301, a second driver 6302, and a third driver 6303 in Embodiment 10. FIG.

FIG. 44 is a diagram showing an overall structure of an eleventh embodiment of the present invention.

FIG. 45 is a diagram showing a motor structure according to the eleventh embodiment.

FIG. 46 is a diagram illustrating a circuit configuration of a command current generator 7050 according to the eleventh embodiment.

FIG. 47 is a diagram showing a circuit configuration of a position detector 7021, a distribution generator 7031, and a distribution corrector 7032 in the eleventh embodiment.

FIG. 48 is a diagram showing a circuit configuration of a current acquisition circuit 7195 in Example 11.

FIG. 49 is a diagram showing a circuit configuration of a first driver 7041, a second driver 7042, and a third driver 7043 in the eleventh embodiment.

FIG. 50 is a diagram showing signal waveforms in the eleventh embodiment.

FIG. 51 is a diagram showing an overall structure according to a twelfth embodiment of the present invention.

FIG. 52 is a diagram showing a circuit configuration of a command current generator 7301 in the twelfth embodiment.

FIG. 53 is a diagram illustrating a circuit configuration of a multiplication commander 7302 according to the twelfth embodiment.

FIG. 54 is a diagram showing a circuit configuration of a command output device 7303 in the twelfth embodiment.

FIG. 55 is a diagram showing a signal waveform according to the twelfth embodiment.

FIG. 56 is a diagram showing an overall structure according to a thirteenth embodiment of the present invention.

FIG. 57 is a diagram showing a motor structure according to a thirteenth embodiment.

FIG. 58 is a diagram showing a circuit configuration of a position detector 7521, a distribution generator 7531, and a distribution corrector 7532 in the thirteenth embodiment.

FIG. 59 is a diagram showing a circuit configuration of a first driver 7541, a second driver 7542, and a third driver 7543 in the thirteenth embodiment.

FIG. 60 is a diagram showing a circuit configuration of a command current generator 7551 according to a thirteenth embodiment.

FIG. 61 is a diagram showing a circuit configuration of a multiplication command unit 7552 in the thirteenth embodiment.

FIG. 62 is a diagram showing a circuit configuration of a command output device 7553 in the thirteenth embodiment.

FIG. 63 is a diagram showing signal waveforms in the thirteenth embodiment.

FIG. 64 is a diagram showing the overall structure of Embodiment 14 of the present invention.

FIG. 65 is a diagram showing a circuit configuration of a position detector 7521, a distribution generator 8031, and a distribution corrector 8032 in the fourteenth embodiment.

FIG. 66 is a diagram showing a circuit configuration of a first driver 8041, a second driver 8042, and a third driver 8043 in the fourteenth embodiment.

FIG. 67 is a diagram showing an overall structure according to a fifteenth embodiment of the present invention.

FIG. 68 is a diagram showing the circuit configuration of a position detector 7521, a distribution generator 8331, and a distribution corrector 8332 in the fifteenth embodiment.

FIG. 69 is a diagram showing a circuit configuration of a correction generator 8510 in the fifteenth embodiment.

FIG. 70 is a diagram showing an overall structure of a sixteenth embodiment of the present invention.

71 is a diagram showing a circuit configuration of a position detector 8701, a distribution generator 8702, and a distribution corrector 8703 in the sixteenth embodiment. FIG.

72 is a diagram showing a circuit configuration of a multiplication command unit 8705 in the sixteenth embodiment. FIG.

FIG. 73 is a diagram showing the overall structure of a seventeenth embodiment of the present invention.

FIG. 74 is a diagram showing a circuit configuration of a position detector 8701, a distribution generator 8902, and a distribution corrector 8903 in the seventeenth embodiment.

FIG. 75 is a diagram showing a circuit configuration of a correction generator 8905 in the seventeenth embodiment.

FIG. 76 is a diagram showing an overall structure of an eighteenth embodiment of the present invention.

77 is a diagram showing a circuit configuration of the first driver 9301, the second driver 9302, and the third driver 9303 in the eighteenth embodiment. FIG.

FIG. 78 is a diagram showing a configuration of a conventional brushless motor.

[Explanation of symbols]

4010, 4510 field magnet parts 4011A, 4011B, 4011C, 4511A, 4
511B, 4511C coil 4012, 4512 position part 4013, 4513 distribution part 4014, 4514 drive part 4015, 4515 command part 4021, 4521, 5701 position detector 4022, 4522, 5022, 5302, 5502,
5702, 5902, 6102 Switching creator 4023, 4523, 5023, 5303, 5503
5703, 5903, 6103 Switching corrector 4031, 4531, 5031 Distributor 4041, 4541, 6301 1st driver 4042, 4542, 6302 2nd driver 4043, 4543, 6303 3rd driver 4050, 4301, 4551 Command current device 4302, 4552, 5705 Multiplier commander 4303, 4553, 5053 Command output device 4060, 4560, 5060, 5310, 5510,
6105 correction generator 4070, 4570, 5070, 5320, 5520,
5905 setting generator 4080, 4580, 5080, 5330, 5530
Correction comparator 7010, 7510 Field magnet unit 7011A, 7011B, 7011C, 7511A, 7
511B, 7511C coil 7012, 7512 position part 7013, 7513 distribution part 7014, 7514 drive part 7015, 7515 command part 7021, 7521, 8701 position detector 7031, 7531, 8031, 8331, 8702,
8902 distribution creator 7032, 7532, 8032, 8332, 8703
8903 Distribution corrector 7041, 7541, 9301 First driver 7042, 7542, 9302 Second driver 7043, 7543, 9303 Third driver 7050, 7301, 7551 Command current device 7302, 7552, 8705 Multiplying commander 7303, 7553 Command output device 7060, 7560, 8510, 8905 Correction generator 7070, 7570, 8520 Command side generator 7080, 7580, 8530 Correction comparator

Claims (46)

[Claims] 1. A field means for obtaining a field flux by a magnetic flux generated by a permanent magnet magnetic pole, a three-phase coil interlinking with the field flux, and a relative position between the field means and the three-phase coil is detected. The position detecting means, the switching generating means for obtaining a three-phase output signal that smoothly changes in response to the output signal of the position detecting means, and the correction signal that changes in proportion to the amplitude of the detection signal of the position detecting means. First, a switching correction means for correcting the amplitude of the output signal of the switching generation means by comparing the correction signal with a predetermined signal, a command means for obtaining an output signal in response to the command signal, an output signal of the command means and the The distribution means for obtaining a three-phase distribution signal that changes smoothly in response to the multiplication result of the output signal of the switching creation means, and the drive signal amplified in power in response to the three-phase distribution signals of the distribution means Drive to supply to phase coil And a brushless motor. 2. The switching generation means and the switching correction means include feedback loop means for correcting the amplitude of the output signal of the switching generation means and the magnitude of the correction signal in response to the comparison result of the correction signal and the predetermined signal. The brushless motor according to claim 1, wherein the brushless motor comprises: 3. The command means obtains a harmonic signal based on the detection signal of the position detecting means, multiplies the command signal by the harmonic signal to obtain a multiplication command current signal containing the harmonic signal component. 3. The brushless motor according to claim 1 or 2, further comprising means for outputting an output signal in response to the multiplication command current signal. 4. The command means obtains two command current signals that respond to the command signal and a harmonic signal that responds to the detection signal of the position detecting means, and commands one of the command current means. A multiplication command means for obtaining a multiplication command current signal by multiplying a current signal and the harmonic signal, and command output means for outputting an output signal obtained by combining the other command current signal of the command current means and the multiplication command current signal. The brushless motor according to any one of claims 1 to 3, which is configured by. 5. The command means according to claim 3 or 4, wherein the command means includes means for obtaining a multiplication command current signal obtained by multiplying a harmonic signal which changes six times per cycle of the detection signal of the position detecting means. The brushless motor according to any one of the above. 6. The switching correction means obtains a harmonic signal in response to the detection signal of the position detection means, obtains a multiplication setting current signal obtained by multiplying a predetermined current signal by the harmonic signal, and obtains the multiplication setting current. 3. The brushless motor according to claim 1, wherein the brushless motor is configured to include a setting creating unit that creates a predetermined signal in response to the signal. 7. The setting generating means obtains two setting current signals and a harmonic signal in response to the detection signal of the position detecting means to obtain one of the setting current signals of the setting current means and the one of the setting current signals. It is configured to include multiplication setting means for obtaining a multiplication setting current signal multiplied by a harmonic signal, and setting output means for outputting a predetermined signal obtained by combining the other setting current signal of the setting current means and the multiplication setting current signal. The brushless motor according to claim 6. 8. The switching correction means is configured to include means for obtaining a multiplication setting current signal obtained by multiplying a harmonic signal that changes six times per cycle of the detection signal of the position detection means.
Alternatively, the brushless motor according to claim 7. 9. The switching correction means obtains an amplitude current signal in response to the amplitude of the detection signal of the position detection means, obtains a harmonic signal in response to the detection signal of the position detection means, and obtains the amplitude current signal and 3. The brushless motor according to claim 1, further comprising a correction creating unit that creates a multiplication correction current signal by multiplying the harmonic signal and creates a correction signal in response to the multiplication correction current signal. . 10. The correction creating means obtains two amplitude current signals which respond to the amplitude of the output signal of the position detecting means, and an harmonic current signal which responds to the detection signal of the position detecting means. A multiplication correction means for obtaining a multiplication correction current signal by multiplying one amplitude current signal of the amplitude current means by the harmonic signal, and a correction signal obtained by combining the other amplitude current signal of the amplitude current means with the multiplication correction current signal. The brushless motor according to claim 9, wherein the brushless motor is configured to include correction output means for outputting. 11. The correction creation means includes means for obtaining a multiplied correction current signal obtained by multiplying a harmonic signal which changes six times per cycle of the detection signal of the position detection means. The brushless motor according to any one of 1. 12. The position detecting means is configured to include means for obtaining two-phase detection signals, and the switching creating means uses the two-phase detection signals to electrically generate a phase difference of substantially 120 degrees. The brushless motor according to any one of claims 1 to 11, wherein the brushless motor is configured to include a means for producing a three-phase output signal having the three-phase output signal. 13. The brushless motor according to claim 12, wherein the position detecting means has only two position detecting elements. 14. A field means for obtaining a field flux by the magnetic flux generated by a permanent magnet magnetic pole, a three-phase coil interlinking with the field flux, and a relative position between the field means and the three-phase coil is detected. A position detecting means, a switching generating means for obtaining a three-phase current signal that smoothly changes in response to an output signal of the position detecting means, and an addition value of unipolar values of the three-phase current signals of the switching generating means, or A switching correction unit that creates a correction signal that changes corresponding to the added value of the absolute values, compares the correction signal with a predetermined signal, and corrects the amplitude of the output signal of the switching creation unit, and an output signal that responds to the command signal. And a distribution means for obtaining a three-phase distribution signal that changes smoothly in response to the multiplication result of the output signal of the command means and the output signal of the switching creation means, and the distribution of the three phases of the distribution means. In response to the signal, the power is amplified And a drive means for supplying the generated drive signal to the three-phase coil. 15. The switching creation means and the switching correction means include feedback loop means for correcting the amplitude of the output signal of the switching creation means and the magnitude of the correction signal in response to the comparison result of the correction signal and the predetermined signal. The brushless motor according to claim 14, wherein the brushless motor comprises: 16. A field means for obtaining a field flux by the magnetic flux generated by a permanent magnet magnetic pole, a three-phase coil interlinking with the field flux, and a relative position of the field means and the three-phase coil. And a position means for correcting the amplitude of the output signal in response to the result of comparison between the correction signal and a predetermined signal. Using a multiplication signal of a harmonic signal and a command signal in response to the detection signal of, in proportion to the command signal,
In addition, command means for producing an output signal containing a harmonic component in response to the multiplication signal at a predetermined ratio, and three-phase that smoothly changes in response to the multiplication result of the output signal of the command means and the output signal of the position means. And a drive unit that responds to the three-phase distribution signals of the distribution unit and supplies a power-amplified drive signal to the three-phase coil. 17. The position means includes feedback loop means for correcting the amplitude of the output signal of the position means and the magnitude of the correction signal in response to the result of comparison between the correction signal and a predetermined signal. 16. The brushless motor according to item 16. 18. The command means obtains two command current signals which respond to the command signal and a harmonic signal which responds to the detection signal of the position means to obtain one command current of the command current means. A multiplication command means for obtaining a multiplication command current signal by multiplying the signal by the harmonic signal, and command output means for outputting an output signal combining the other command current signal of the command current means and the multiplication command current signal. The brushless motor according to claim 31 or claim 17, which is configured. 19. The command means includes a means for obtaining a harmonic signal that changes six times per cycle of the detection signal of the position means and obtaining a multiplied command current signal by multiplying the command signal and the harmonic signal. The brushless motor according to any one of claims 16 to 18, which is provided. 20. A field means for obtaining a field magnetic flux by a magnetic flux generated by a permanent magnet magnetic pole, a three-phase coil interlinking with the field magnetic flux, and a relative position of the field means and the three-phase coil are detected. Position detecting means, switching creating means for obtaining an output signal that changes smoothly in response to the detection signal of the position detecting means, and a harmonic signal in response to the detection signal of the position detecting means to obtain the harmonic signal. And a current signal are multiplied to create a multiplied current signal containing a harmonic signal component, and a switching correction means for correcting the amplitude of the output signal of the switching generation means in response to the multiplied current signal and a command signal A command means for obtaining an output signal, and a smooth change in response to the multiplication result of the output signal of the command means and the output signal of the switching creating means 3
A brushless motor comprising: a distribution unit that obtains a phase distribution signal; and a drive unit that responds to the three-phase distribution signals of the distribution unit and that supplies a power-amplified drive signal to the three-phase coil. 21. The switching correction means obtains a harmonic signal in response to a detection signal of the position detection means, obtains a multiplication setting current signal obtained by multiplying a predetermined current signal by the harmonic signal, and obtains the multiplication setting current. Setting generating means for generating a predetermined signal in response to the signal, correction generating means for generating a correction signal in response to the amplitude of the detection signal of the position detecting means, and the switching in response to the result of comparison between the correction signal and the predetermined signal. 21. The brushless motor according to claim 20, further comprising a correction comparing unit that corrects the amplitude of the output signal of the creating unit. 22. The setting creating means obtains two setting current signals, a setting current means, and a harmonic signal in response to the detection signal of the position detecting means, and one setting current signal of the setting current means and the setting current signal. It is configured to include multiplication setting means for obtaining a multiplication setting current signal multiplied by a harmonic signal, and setting output means for outputting a predetermined signal obtained by combining the other setting current signal of the setting current means and the multiplication setting current signal. The brushless motor according to claim 21. 23. The setting generation means includes a means for obtaining a multiplication setting current signal obtained by multiplying a harmonic signal that changes six times per cycle of the detection signal of the position detection means. The brushless motor according to any one of 1. 24. The switching correction means obtains an amplitude current signal in response to the amplitude of the detection signal of the position detection means, obtains a harmonic signal in response to the detection signal of the position detection means, and outputs the amplitude current signal as the amplitude current signal. A correction creation unit that creates a multiplication correction current signal by multiplying the harmonic signal to create a correction signal that responds to the multiplication correction current signal, a setting creation unit that creates a predetermined signal, and a comparison result of the correction signal and the predetermined signal. 21. The brushless motor according to claim 20, further comprising a correction comparison unit that corrects the amplitude of the output signal of the switching generation unit in response to the above. 25. The correction creating means obtains two amplitude current signals which respond to the amplitude of the detection signal of the position detecting means, and an harmonic current signal which responds to the detection signal of the position detecting means, A multiplication correction means for obtaining a multiplication correction current signal by multiplying one amplitude current signal of the amplitude current means by the harmonic signal, and a correction signal obtained by combining the other amplitude current signal of the amplitude current means with the multiplication correction current signal. 25. The brushless motor according to claim 24, comprising a correction output means for outputting. 26. The correction creating means includes a means for obtaining a multiplied correction current signal obtained by multiplying a harmonic signal which changes six times per cycle of the detection signal of the position detecting means. The brushless motor according to any one of 1. 27. A field means for obtaining a field magnetic flux by a magnetic flux generated by a permanent magnet magnetic pole, a three-phase coil interlinking with the field magnetic flux, and a relative position of the field means and the three-phase coil are detected. Position detecting means, command means for obtaining an output signal in response to the command signal, and smooth change in response to the output signal of the position detecting means, and 3 in response to the output signal of the command means.
Distribution generating means for obtaining a phase distribution signal, and a correction signal that changes in proportion to the amplitude of the detection signal of the position detecting means are generated, and the distribution is made by substantially comparing the correction signal and the output signal of the commanding means. Brushless comprising: distribution correction means for correcting the amplitude of the distribution signal of the creating means; and driving means that responds to the three-phase distribution signals of the distribution creating means and supplies a power-amplified drive signal to the three-phase coil. motor. 28. The distribution creating means and the distribution correcting means substantially compare the correction signal and the output signal of the command means, and in response to the comparison result, the amplitude of the distribution signal of the distribution creating means and the correction signal 28. The brushless motor according to claim 27, comprising a feedback loop means for correcting the size. 29. The commanding means obtains a harmonic signal in response to the detection signal of the position detecting means, multiplies the command signal by the harmonic signal, and obtains a multiplication command current signal containing a harmonic signal component. 29. The brushless motor according to claim 27, further comprising means for producing an output signal in response to the multiplication command current signal. 30. The command means obtains two command current signals which respond to the command signal and a harmonic signal which responds to the detection signal of the position detecting means to obtain one command of the command current means. A multiplication command means for obtaining a multiplication command current signal by multiplying a current signal and the harmonic signal, and command output means for outputting an output signal obtained by combining the other command current signal of the command current means and the multiplication command current signal. 30. The brushless motor according to claim 27, wherein the brushless motor comprises 31. The commanding means is configured to include means for obtaining a multiplication command current signal obtained by multiplying a harmonic signal which changes six times per cycle of the detection signal of the position detecting means.
Alternatively, the brushless motor according to claim 30. 32. The distribution correction means obtains an amplitude current signal in response to the amplitude of the detection signal of the position detection means, obtains a harmonic signal in response to the detection signal of the position detection means, and obtains the amplitude current signal as 29. The brushless motor according to claim 27, further comprising a correction creating unit that creates a multiplication correction current signal by multiplying the harmonic signal and creates a correction signal in response to the multiplication correction current signal. . 33. The correction creating means obtains an amplitude current means for obtaining two amplitude current signals in response to the amplitude of the detection signal of the position detecting means, and a harmonic signal in response to the detection signal of the position detecting means. A multiplication correction means for obtaining a multiplication correction current signal by multiplying one amplitude current signal of the amplitude current means by the harmonic signal, and a correction signal obtained by combining the other amplitude current signal of the amplitude current means with the multiplication correction current signal. 33. The brushless motor according to claim 32, comprising a correction output means for outputting. 34. The correction creating means includes a means for obtaining a multiplied correction current signal obtained by multiplying a harmonic signal which changes six times per cycle of the detection signal of the position detecting means. The brushless motor according to any one of 1. 35. The position detecting means is configured to include means for obtaining two-phase detection signals, and the distribution creating means uses the two-phase detection signals to electrically generate a phase difference of substantially 120 degrees. The brushless motor according to any one of claims 27 to 34, which is configured to include a means for generating a distribution signal of the three phases. 36. The brushless motor according to claim 35, wherein the position detecting means has only two position detecting elements. 37. A field means for obtaining a field magnetic flux by a magnetic flux generated by a permanent magnet magnetic pole, a three-phase coil interlinking with the field magnetic flux, and a relative position between the field means and the three-phase coil are detected. Position detecting means, command means for obtaining an output signal in response to the command signal, and smooth change in response to the output signal of the position detecting means, and 3 in response to the output signal of the command means.
Distribution generating means for obtaining a phase distribution signal, and a correction signal that changes corresponding to the added value of the unipolar values or the added value of the absolute values of the three-phase current signals in response to the detection signal of the position detecting means, A distribution correction means for substantially comparing the correction signal with the output signal of the command means to correct the amplitude of the distribution signal, and a drive signal which is power-amplified in response to the three-phase distribution signals of the distribution creating means. And a drive means for supplying the three-phase coil to the brushless motor. 38. The distribution creation means and the distribution correction means substantially compare the correction signal and the output signal of the command means, and in response to the comparison result, the amplitude of the distribution signal of the distribution creation means and the correction signal. 38. The brushless motor according to claim 37, comprising a feedback loop means for correcting the size. 39. A field means for obtaining a field magnetic flux by a magnetic flux generated by a permanent magnet magnetic pole, a three-phase coil interlinking with the field magnetic flux, and a relative position of the field means and the three-phase coil are detected. Position detection means, and a harmonic signal responding to the detection signal of the position detection means and a multiplication signal of the command signal are used, and a harmonic component proportional to the command signal and responsive to the multiplication signal has a predetermined ratio. Commanding means for producing an output signal including: distribution generating means for smoothly changing in response to the output signal of the position detecting means to obtain a three-phase distribution signal in response to the output signal of the commanding means; and the position detection Distribution correction means for creating a correction signal that changes in response to the amplitude of the detection signal of the means, and substantially comparing the correction signal with the output signal of the command means to correct the amplitude of the distribution signal of the distribution creation means. , The distribution creation A brushless motor that responds to the three-phase distribution signal of the means and supplies a power-amplified driving signal to the three-phase coil. 40. The distribution creating means and the distribution correcting means substantially compare the correction signal and the output signal of the command means, and in response to the comparison result, the amplitude of the distribution signal of the distribution creating means and the correction signal. 40. The brushless motor according to claim 39, comprising feedback loop means for correcting the size. 41. The command means obtains two command current signals that respond to the command signal and a harmonic signal that responds to the detection signal of the position detecting means, and commands one of the command current means. A multiplication command means for obtaining a multiplication command current signal by multiplying a current signal and the harmonic signal, and command output means for outputting an output signal obtained by combining the other command current signal of the command current means and the multiplication command current signal. The brushless motor according to claim 39 or 40, which is configured by 42. The commanding means includes means for obtaining a harmonic signal that changes six times per cycle of the detection signal of the position detecting means and obtaining a multiplication command current signal obtained by multiplying the command signal and the harmonic signal. 42. The brushless motor of claim 41 configured. 43. Field means for obtaining a field magnetic flux by the magnetic flux generated by a permanent magnet magnetic pole, three-phase coils interlinking with the field magnetic flux, and relative positions of the field means and the three-phase coil are detected. Position detecting means, command means for obtaining an output signal in response to the command signal, and three-phase distribution signals that respond to the output signal of the position detecting means, change smoothly, and respond to the output signal of the command means. A distribution creating means for obtaining and an amplitude signal responsive to the amplitude of the detection signal of the position detecting means are created, and the amplitude signal is generated by using the multiplication result of the harmonic signal and the amplitude signal responsive to the detection signal of the position detecting means. Distribution correction means for correcting the amplitude of the distribution signal by obtaining a correction signal that is proportional to and that includes a harmonic component in a predetermined ratio, and substantially comparing the correction signal with the output signal of the command means. The three phases of the distribution creation means A brushless motor comprising: a driving unit that responds to a distribution signal and supplies a power-amplified driving signal to the three-phase coil. 44. The distribution correction means obtains an amplitude current signal in response to the amplitude of the detection signal of the position detection means, obtains a harmonic signal in response to the detection signal of the position detection means, and obtains the amplitude current signal and Compensation generating means for producing a multiplication correction current signal by multiplying the harmonic signal and producing a correction signal in response to the multiplication correction current signal, and the correction signal and the output signal of the command means are substantially compared, and the comparison result 44. The brushless motor according to claim 43, further comprising correction comparing means for correcting the amplitude of the distribution signal of the distribution creating means and the magnitude of the correction signal in response to the above. 45. The correction creating means obtains two amplitude current signals which respond to the amplitude of the detection signal of the position detecting means, and an harmonic current signal which responds to the detection signal of the position detecting means. A multiplication correction means for obtaining a multiplication correction current signal by multiplying one amplitude current signal of the amplitude current means by the harmonic signal, and a correction signal obtained by combining the other amplitude current signal of the amplitude current means with the multiplication correction current signal. 45. The brushless motor according to claim 44, comprising a correction output means for outputting. 46. The correction generating means is configured to include means for obtaining a multiplied correction current signal obtained by multiplying a harmonic signal which changes 6 times per cycle of the detection signal of the position detecting means. The brushless motor according to any one of 1.