JPH0828677B2 - Broadband wireless transmission system - Google Patents

Description

Description: FIELD OF THE INVENTION The present invention relates generally to wireless transmission systems, and in particular to wideband where discrete frequency components are generally below the noise level and thus are indistinguishable from conventional wireless receivers. It is about the type system.

Wireless transmission of communication signals, eg audio signals, is usually done by one of two methods. One is called an amplitude modulation system, where the sinusoidal radio frequency carrier is an intelligent signal, that is, the amplitude of the communication signal is modulated, and when the signal is received at the receiving place, the reverse processing, that is, the demodulation of the carrier wave reproduces the communication signal. To be done. Another system is called frequency modulation, where the carrier signal is frequency modulated instead of amplitude modulated. When a frequency-modulated signal, i.e. an FM signal, is received, what is called discrimination, i.e. the frequency change is performed by changing the amplitude according to the original modulation, thereby causing the circuit performing the reproduction of the communication signal. Adopted. In any system, there is basically a sinusoidal carrier that is assigned and occupies a well-defined frequency band or channel, which occupies a spectral space that cannot be utilized by other transmissions within its scope. At present, spectral space is being used almost everywhere, and there is an urgent need for some way to extend the utilization of communication channels. In view of such circumstances, instead of using the conventional method of using discrete frequency channels for wireless transmission link, a wider frequency range in which the transmitted intelligence band can be extended over a range of 10 to 100 times. A spectrum has been adopted, but the energy of any single frequency forming this spectrum is very low, and wireless communication links have been proposed that are generally below normal noise levels. Thus, it will be appreciated that this type of transmission is substantially non-interfering with other services. Using this method, it has been proposed to employ some degree of coded sequence modulation and to make each such communication link incoherent with a different coded sequence having tunable characteristics.

Problems to be Solved by the Invention However, importantly, as far as the applicant knows,
Nobody has developed a practical system yet.

Therefore, it is an object of the present invention to extend the spectral range of wideband spectrum communications to operate at 1,000 to 1,000,000 times or more, and rather very simple and low, rather than to say 10 to 100 times the intelligence modulation factor. It is to provide a wideband communication system that can be achieved with an inexpensive electronic assembly.

Another object of the present invention is to provide a radio receiver that meets the above requirements.

Means and Actions for Solving the Problems According to the present invention, a fixed or programmed rate pulse signal is modified or modulated with respect to the rising edge of the pulse turning off as a function of each intelligence signal. The resulting pulse signal turns on or triggers an avalanche mode operating semiconductor switch powered through a delay line or other similar short duration power supply that is charged at the time of the trigger pulse. This switch is turned off in the time range of a few picoseconds to 50 nanoseconds.

That is, one of the important components of the wideband transmission system according to the present invention is the control signal input means for switching and turning on the avalanche semiconductor switch in response to the output of the pulse train generating means, the excursion power input, and the switching power. Output and power on for the switching power output
/ OFF switching means, and a delay line coupled to the power input and providing a delay of 1 picosecond to 50 nanoseconds and a delay charging means coupled to the delay line to charge the delay line between pulses of the pulse train. Therefore, the switching means is provided with a DC bias means which is turned on by the output of the pulse generating means and turned off by the exhaustion of electric power from the delay line.

The resulting pulsed output of this switch is coupled to a non-resonant transmit antenna that is coupled to the atmosphere or space for transmission.

That is, one of the important requirements of the receiving unit of the system according to the present invention is to output the discrete electric pulse that receives the wide band signal from the non-resonant antenna that radiates the wide band signal and each realizes the pulse position modulation. The non-resonant receiving antenna means provided is provided.

Receiving of the transmission is done by a receiver that performs detection synchronously by desensitizing detection during pulse signal anticipation.

That is, one of the important constituent features of the receiver according to the present invention is a reception which comprises a non-resonant antenna, receives a plurality of transmissions from the transmission antenna, and outputs a plurality of electric pulses responsive to a plurality of transmission pulse signals. An antenna means, an amplifying means for amplifying a plurality of received pulses in response to the output of the antenna means, and a signal responsive to the output of the amplifying means, and a generated average of the plurality of pulses received by the receiving means. Signal sensing windowing means responsive to a plurality of signals each appearing in the time window of occurrence and a single output for the plurality of signals, each of which generally matches time, and a plurality of received signals appearing during the occurrence of the time window. And a signal for converting the output of the detection means into a single signal replica of the plurality of intelligence signals. And the step, in response to an output of the signal conversion lies in comprising a signal reproducing means for reproducing said series of intelligence signals.

One of further important constitutional requirements is that the wideband transmission system and receiver according to the present invention convert the output of the synchronous detection means into a single signal copy of the plurality of intelligence signals, and the signal conversion. And a means for reproducing the plurality of intelligence signals in response to the means.

EXAMPLE 1 In FIG. 1, first, for transmitter 10, a fundamental frequency of 100 KHz is generated by oscillator 12. Oscillator 12 is generally comprised of a crystal controlled oscillator that includes conventional circuitry that produces a square wave at 100 KHz as an output. This pulse signal is applied to the 4-division divider 14 and 25KH from its output terminal.
A square wave shown by waveform A in FIG. In the following, when instructing the waveforms shown in FIG. 4, all are instructed by character codes and “FIG. 4” is omitted. The output from the frequency divider 14 is used as a general transmission signal and as an input to the power supply 16. The power supply 16 is a controlled type,
This also applies a DC deviation voltage of 300 V to the output section 18 of the transmitter 10 that oscillates at 25 KHz on a non-interference basis.

The output of the divide-by-four divider 14 is used as the signal base, and therefore the pulse position modulator via the capacitor 20.
It is applied to 22. The pulse position modulator 22 has at its input,
It includes an RC circuit consisting of a resistor 24 and a capacitor 26, which converts the rectangular wave input into a substantially triangular wave as shown by waveform B and applies it across resistor 25 to the non-inverting input of comparator 28.
This non-inverting input of comparator 28 is also applied with a selected or reference positive voltage filtered by capacitor 27, which is supplied from + 5V terminal 29 of DC bias power supply 30 via resistor 32. Thus, for example, at the non-inverting input, in effect, an upwardly positively displaced triangular wave, as shown by waveform C, appears.

The net conductive level of comparator 28 is provided to the inverting input of comparator 28 through capacitor 36 and across resistor 37 and to resistor 38.
Determined by the audio signal input from the microphone 34 which is biased by the power supply 30 across the resistor 32 through the. The audio signal on which the excursion voltage is superimposed has a waveform D
Is illustrated in. As a result of superimposing the input like this,
At the output of the comparator 28, the triangular wave signal 40 (waveform E) is a modulation signal.
When the value is higher than 42, it rises to the positive saturation level, while when it is larger than the triangular wave signal 40, it falls to the negative saturation level. The output signal of comparator 28 is shown as waveform F.

In the case of this example, the inventors are interested in adopting the falling edge 44 (waveform F) of the output of the comparator 28, and
It should be noted that this fall changes in time as a function of the signal modulation. The falling edge of the pulse in waveform F triggers on the monostable multivibrator 46, which has an on-time of approximately 50 nanoseconds, the output of which is shown in waveform G. For purposes of illustration, the relevant rising or falling edges of the relevant waveforms are properly aligned, but the pulse width and spacing (indicated by dashed lines, spacing is 40 μs) is irrelevant on scale. . Thus, the rising edge of pulse waveform G corresponds in time to the falling edge of waveform F, and its time position within the average time between the pulses of waveform G changes as a function of the input audio modulation signal to comparator 28.

The output of the monostable multivibrator 46 is the diode 48
Operates as a trigger amplifier across the resistor 50 through
Applied to the base input of NPN transistor 52. The transistor amplifier 52 has a resistor 54 (e.g., 1.
5KΩ) and is biased from the + 5V terminal 29 of the 5V power supply 30 to its collector. Capacitor 5 with a capacitance of about 1 mf
6 is connected between the collector of transistor 52 and ground to apply a full excursion potential across transistor 52 during its short turn-on period of 50 nanoseconds. Transistor
The output of 52 is coupled to the primary winding 58 of the trigger transformer 60 between its emitter and ground. Trigger transformer 60
Two similar secondary windings 62 and 64 independently energize the respective base-emitter inputs of the two avalanche or avalanche mode operating NPN transistors 66 and 68 of the power output section 18. Although two are shown in the figures, more than one or two may be provided when properly combined.

There are many types of avalanche mode operating transistors 66 and 68 that have metallization, but when triggered on, their resistance drops (eg, about
This condition is maintained until the collector current is sufficiently cut off (at several μA). Their respective collector-emitter circuits are connected in series, to which a + 300V collector bias is connected in parallel across the filter capacitor 72 from the power supply 16 and via the resistor 74.
It is applied to one end 76 of DL. Although the delay line DL is shown to have three parts S _{1 to} S ₃ , it is generally used to have 5 to 10 parts. Each line may consist of a RG58 type coaxial cable, about 3 inches long, required to fully realize about 3 nanosecond pulses. Resistance as shown
The positive input potential from 74 is connected to the center conductor of each delay line, and the outer conductors are grounded. The resistor 74 is
It is in the range of 50 KΩ and is selected so that the delay line DL can be charged in about 1 μsec. The voltage divider resistors 71 and 73 are typically equal to 1 megΩ each and provide a load balancing function between transistors 66 and 68. The delay line DL consists of both transistors 66 and 68.
Is charged to 300V during the turn-off period, ie, between input pulses. When the respective inputs to transistors 66 and 68 are triggered on by a trigger pulse, both transistors begin to conduct within 0.5 nanoseconds, and because of the low voltage drop across them (which is characteristic of them). When operating in avalanche mode) approximately 120V appears as a pulse across the output resistor 78 (eg, 50Ω).

Importantly, the turn-on edge, or rising edge, of this pulse is made by the trigger pulse applied to the respective inputs of transistors 66 and 68, and the rising edge of this output pulse is determined by the discharge time of delay line DL. . By this method, and by selecting the length of the delay lines and the choice of Q, pulses of good shape and very short, ie in the 3 nanoseconds and peak power of about 300 W, are generated. Following turn-off, the delay lines are recharged via resistor 74 before the arrival of the next trigger pulse. Power output 18 as will become apparent later
Has a very simple structure and is composed of completely inexpensive circuit elements. For example, transistors 66 and 68 are available for a price of about $ 0.12.

The output of the power output section 18 appears across the resistor 78 and is supplied to the time range shaping filter 82 via the coaxial cable 80.
The latter is used to attach a selected signature to the output as an encoded or certified signal format. Alternatively, the filter 82 may be omitted if such safety measures are not considered necessary, and to illustrate this, the bypass line 84 including the switch 86 is schematically illustrated as such omission. ing.

The signal output of the filter 82 or the output of the power output unit 18 is directly applied to the discone antenna 90, which is a non-resonant antenna, via the coaxial cable 88. This type of antenna radiates all signals at frequencies above its cut-off frequency as a function of size, eg above about 50 MHz for relatively small units. In any case, the antenna 90 radiates a broadband signal, an example of which is shown in the time range in waveform H, which waveform, when the filter 82 is used, has its shaping effect and, to some extent, that of a discone antenna. Is a composite of.

The output of the discone antenna 90 is generally transmitted over a discrete space and then received by a discone antenna 92 of a similar receiver 96 at a second location, as shown in FIG. Will be done. Although the waveform may be slightly distorted by transmission, for purposes of illustration it is assumed that the received waveform is a duplicate of waveform H. The received signal is amplified by a wide band amplifier 94 having a wide band frequency response over the range of the transmitted signal. If a filter 92 is employed in transmitter 10, a correspondingly configured filter 98 will be employed. As an illustration when a matched filter is not employed, a switch 100 connecting the input and output of the filter 98 is shown schematically, and closing it indicates that the filter 98 is bypassed. Matched filter
The output of the wideband amplifier is illustrated in waveform I as a single amplification replica of waveform H, assuming that 98 is not employed.
In either case, the waveform appears across resistor 101.

The signal waveform I is applied to the synchronous detector 102. This detector 102 basically consists of an avalanche transistor 1
It has two functional units: 04 and adjustable monostable multivibrator 106. Monostable multivibrator 106
Is driven by an input across an emitter resistor 110 connected between avalanche transistor 104 and ground.
The avalanche transistor 104 includes a variable voltage DC power supply 112 via a variable resistor 114 (eg, 100 KΩ to 1 MΩ).
(Eg, 100 to 130V). Delay line 1
16 is connected between the collector of transistor 104 and ground,
It provides an effective operating bias for transistor 104 and is charged between conduction times, as described below.

Now, assuming that a charging interval has just occurred, the avalanche transistor 104 is switched on or triggered by a signal applied to its base-emitter from filter 98 across resistor 101. Further assume that this triggering is enabled by the output of monostable multivibrator 106 going high (waveform J). When triggered, the conduction of the avalanche transistor 104 produces a rising voltage (waveform K) across the emitter resistor 110, which triggers the monostable multivibrator 106 to pull its output low. This causes the diode 108 to conduct and thus the avalanche transistor 1
The input to 04 eventually shorts. This phenomenon occurs within 2 to 20 nanoseconds from the positive rising edge of the input signal (waveform I). The conduction period of the transistor 104 is accurately set by the charge capacitance of the delay line 116. Using a delay line consisting of a 12 inch RG58 coaxial cable and with a charging voltage of about 110V, this conduction period is set to about 2 nanoseconds, for example. With 1 to 25 parts of coaxial cable, 0.25 to 300 inches in length, a good variation in on-time is obtained.

The monostable multivibrator 106 is adjustable and sets a switching time for its output to return high at a selected time and subsequently is triggered as previously described. When this occurs, the diode 108 is turned off again, removing the short-circuit condition on the base input of the avalanche transistor 104, making the transistor 104 sensitive to incoming signals. This phenomenon occurs, for example, at time T ₁ of waveform J. The delay time before switching by the monostable multivibrator 106 depends on the avalanche amplifier 10
Sensitivity to 4 is set to update at time T ₁ just before a significant signal is expected to occur. It will be noted that this will be shortly before the generation of the signal pulse of waveform I. Thus, with a repetition rate of 25 KHz for a significant signal, as already mentioned, the monostable multivibrator
106 will be set to switch its output from low to high after a period of about 40 μsec, or 40,000 nanoseconds. Considering that the width of the positive portion of the input pulse is only about 20 nanoseconds, thus, the synchronous detector 102 is insensitive during most of the time. Sensitive windows are illustrated as existing between time points T ₁ and T ₂ and their duration is monostable multivibrator 10.
Adjustable by 6 conventional timing adjustments. Generally, the adjustment is made to be fairly wide initially to provide enough windows to lock the signal rapidly and then to provide a narrower window for maximum compression ratio.

Output signal of avalanche transistor 104 (waveform K)
Is a constant-width pulse train with rising edges that vary as a function of modulation. One type of pulse position modulation that exists is obtained. This appears across the emitter resistor 110,
From the emitter of the transistor 104 to the active low pass filter 117
Is supplied to. This fluctuating pulse signal is converted into a baseband intelligence signal by the low-pass filter 117, demodulated, and then supplied to the audio amplifier 119, where it is amplified. The output of this amplifier 119, assuming an audio transmission as illustrated here, is a loudspeaker 120.
To be played by it. If it is something other than an intelligence signal, then appropriate demodulation may be done to detect the existing modulation.

It should be noted that the above receiver 96 has two characteristics especially for tuning: sensitivity and window duration. Sensitivity is adjusted by adjusting the variable voltage power supply 112, and "lock-on" is done by tuning the duration of the high output state of the monostable multivibrator 106 as described above. In general, this time period will be adjusted to the minimum required to capture the excursion range of the position modulated signal pulse.

FIG. 3 illustrates an alternative type of detector 122 used for receiver 96. In other words, this synchronous signal detector, a form of synchronization signal detection is performed by using a ring demodulator 124 of four matched diodes D ₁ to D _4. In general, this demodulator has a resistor 101
Act as a single pole, single throw switch or simply gate with the input appearing across and applied to input terminal I. The gate output appears at the terminal O, passes through the capacitor 113 and the resistor 115, and is supplied to the input of the active low-pass filter 117 having a demodulation function. The ring demodulator 124 has a fourth
The gate is opened by the pulse PG applied to the terminal G, which is illustrated by the broken line in the waveform L of the figure. The pulse PG is generated by a monostable multivibrator 126 controlled by a VCO (voltage controlled oscillator) 127. VCO127 has a waveform L
Is controlled so as to be synchronized with the average rate of the incoming signal indicated by the solid line. To accomplish this, the output voltage from the ring demodulator 124 is VCO127 across resistor (128) across capacitor (130) connected to the control input of VCO127 (averaging).
Is supplied to. The signal frequency output of the VCO 127 controlled in this way is supplied to the input of the monostable multivibrator 126, and the output gate pulse PG is output therefrom. This pulse is rectangular as shown and has a selected pulse width of generally 2 to 20 nanoseconds, the selection being made by time modulation of the transmitted pulse. This pulse is provided to the primary winding of the pulse transformer 132, the secondary side of which is coupled to the gate terminal G of the ring demodulator 124. The diode 134 is connected to the secondary side of the transformer 132, effectively eliminating the negative conversion that would occur if the pulse output of the monostable multivibrator 126 was applied to the transformer 132 if the diode was not connected. Acts to prevent. In this way, the gate pulse PG acts to bias all the diodes of the ring demodulator 124 that are conducting for its duration, thereby gating the signal input from terminal I to terminal O. As mentioned above, this signal input is
It is applied to the input of the low pass filter 117 through the resistor 115 through the resistor 3.

The function of the detector 122 is to provide the low pass filter 117 with the portion of the input signal (shown by waveform L in FIG. 4) that appears within the limits of the gate pulse PG. Gate pulse PG
The time portion of VCO127 is set at the timing of the pulse output of VCO127, and the output rate of VCO127 appears across VCO127.
Determined by voltage input to 127. Capacitor 130
Is chosen to have a slightly lower time constant than that corresponding to the lowest modulation frequency to be demodulated. Thus, VC
The output pulse rate of O127 is such that the pulse position of the gate pulse is not changed during the modulation induction time position of the input signal (illustrated by the solid line in waveform H). As a result, the demodulator 124
The average value of the signal gated through will change as a function of the modulation originally applied to that signal. This average value is converted into an amplitude-type intelligence signal by passing through the low-pass filter 117. It is then amplified as desired by audio amplifier 119 and then reproduced by loudspeaker 120.

It will be appreciated that the Applicant has provided an inexpensive and practical broadband communication system. This system uses an avalanche mode gated transistor, which is charged from a delay line, and when a modulation induced variable position pulse is applied, the variable position pulse has a width of 1 to 3 nanoseconds. Is output. This, of course, can result in a broad spectrum starting at about 50 megacycles and extending to the 500 megacycles. Thus, with an audio frequency of, for example, 5,000 Hz, the energy radiated to transmit this signal is distributed and spread almost incredibly 100,000 times. As a result, there is almost no interference with conventional limited band signals. As an example of the effectiveness of such a system, still using a 20-cent transistor operating in avalanche mode, an audio-modulated audio rising-modulation pulse is provided as an output with a peak power of about 280W. Was done. The signal received at a distance of 200 feet had a peak voltage of about 1V into a 50Ω load. actually,
It has been found that the power level required to receive is on the order of a few μW, so the effective range at this power level is considerable. At the same time, from the spectrum analyzer installed at the receiving point, the presence of any signal,
There was no possibility of interference with other services. In fact, given the spectral distribution of the transmitted signal, the existing level that might interfere with a standard signal, eg a 5 KHz wide signal, would be in the 2.8 μW range at the antenna location. One way to describe the superiority of this type of transmission over the prior art is that in the example above, the power appears substantially during a period of 3 nanoseconds and then every 1,000,000 nanoseconds. It is important to note that. That is, it has a natural power ratio of 33,000: 1. In that case, by limiting the listening period for that signal to substantially its pulse width, the receiving circuit need only be concerned with the appearance of the pulse in the micro window. Therefore, the overall S / N (signal / noise) ratio is extremely large. Furthermore, it should be understood that a slightly different repetition rate could be employed to accommodate a very large number of users and even this could be extended by a discrete pattern of pulse timing. Both analog and digital patterns can be adopted, for example,
Modulated pulse-based dithering can be performed with similar or complementary dithering employed at the receiving end. In fact, highly confidential communications can be easily achieved, even for recipients who are generally only aware of the existence of this type of communications, with little or no degree of complexity. In addition to the above, the application of this system to radar and motion detectors is virtually limitless, enabling the delay-free detection required for the often required signal integration.

[Brief description of drawings]

FIG. 1 is a schematic combination block circuit configuration diagram of a wideband transmitter according to the present invention, FIG. 2 is a schematic combination block circuit configuration diagram of a wideband receiver according to the present invention, and FIG. 3 is the synchronization shown in FIG. FIG. 4 is a schematic block diagram of a combinational block circuit of another type of the active detector, and FIG. 4 shows electric signal waveforms in respective parts of the circuit system shown in FIGS. 1 and 2.

Claims (17)

[Claims] 1. A pulse generating means for outputting a pulse repeatedly generated at a selected time interval, a source of a series of intelligence signals, and a pulse generator in response to the pulse generating means and the intelligence signal source. A radio transmitter comprising a modulator means for producing as output a pulse train whose rising edge varies as a function of each said intelligence signal at a time position; a control signal input, a displacement power input and a switching power output responsive to said output of said modulator means An avalanche semiconductor switch means for switching on / off power to the power output, a delay line coupled to the excursion power input and providing a delay of 1 picosecond to 50 nanoseconds and the delay line. And a DC bias source comprising delay line charging means for charging the delay line between the pulses of the pulse train. Transmitting antenna means comprising a non-resonant antenna connected to the space and coupled to the switched power output for transmitting a signal received from the switched power output, and a plurality of transmissions from the transmit antenna means comprising a non-resonant antenna Receiving antenna means for receiving a plurality of electric pulses and outputting a plurality of electric pulses in response to a plurality of transmitting pulse signals; amplifying means for amplifying a plurality of receiving pulses in response to an output of the receiving antenna means; and responding to an output of the amplifying means Responsive to a plurality of signals appearing within a repeating time window, each signal generally corresponding to an average time of occurrence of a plurality of pulses received by said receiving means, and a single output for said plurality of signals. Signal-sensing windowing means for generating noise, and insensitive means for not sensing a plurality of received signals appearing during generation of the time window And a signal converting means for converting the output of the synchronous detecting means into a single signal copy of the plurality of intelligence signals, and reproducing the plurality of intelligence signals in response to the output of the signal converting means. A broadband wireless transmission system comprising: a radio receiver comprising a signal reproducing means. 2. The avalanche semiconductor switch means comprises:
Claim: At least one avalanche transistor connected in a common emitter configuration having the switched power output between its emitter and common ground, having a base as the control signal input and further having a collector as the excursion power input. The system as described in the first section of the scope. 3. The charging means comprises a DC power source having a voltage equal to or higher than the avalanche potential of the semiconductor switch means, and the excursion power input and the switching power output are both
The DC power supply, which comprises a first terminal and a second terminal, and wherein the charging means further has a value that causes the voltage across the avalanche semiconductor switch means to drop to substantially zero when the avalanche semiconductor switch means enters an avalanche state. A system according to claim 1, comprising a resistor connected between the first terminal and the first terminal. 4. The system of claim 3 wherein said non-resonant antenna of said transmit antenna means is coupled between said second terminal and said DC power supply. 5. The delay line comprises 1 to 25 coaxial cables having a length of 0.25 ″ to 300 ″, one end of an inner conductor of each of the coaxial cables being connected to the collector, The system of claim 2 wherein the outer conductor of the wire is grounded and the opposite end of the inner conductor is an open end. 6. The system of claim 3 wherein said avalanche semiconductor comprises a transistor, said transistor including an emitter coupled to said transmit antenna means. 7. The switch means comprises at least two avalanche transistors having collector-emitter circuits connected in series, a resistor and a power output connected to the emitter of one of the transistors, and the DC bias source is the DC bias source. 7. A system as claimed in claim 6 connected to a resistor and to another collector of the avalanche transistor. 8. The synchronous detection means comprises an avalanche transistor having a signal input connected to the output of the amplifying means, the avalanche transistor receiving the input of the avalanche transistor in response to a rising edge of its signal output. The system of claim 1 including adjustable gate means for disabling a selected time period between the recurring time windows. 9. The synchronous detection means: a ring demodulator means having a gate input, a signal input and a signal output constituting the output of the synchronous detection means; responsive to an average output of the outputs of the ring demodulator means. And a voltage controlled oscillator means for generating a pulse output at a frequency corresponding to the average output of the outputs of the ring demodulator means; and one of the repeatedly generated time windows in response to the output of the voltage controlled oscillator means. A system as claimed in claim 1 comprising gating means for providing a gated input signal having a selected duration defining a window to said ring demodulator means. 10. The gating means comprises: a monostable multivibrator having an input and an output coupled to the voltage controlled oscillator means; and the output of the monostable multivibrator and the gate input of the ring demodulator means. A system as claimed in claim 9 comprising a pulse transformer connected in between. 11. The system of claim 1 wherein said signal converting means comprises an active low pass filter. 12. Pulse generating means for generating a repetitive pulse train; avalanche semiconductor switching means, control means for responding to the output of said pulse generating means for turning on this means, deviation power input means, Switching power output means; coupled to the excursion power input means, and from 1 picosecond to 50
It comprises a delay line providing a nanosecond delay and delay line charging means coupled to the delay line for charging said delay line between pulses of said pulse train, whereby said switch means is turned on by the output of said pulse generating means. A direct current bias source that is turned off due to depletion of power from the delay line; coupling means coupled to the switching power output means and a transmission medium for coupling a signal from the switching power output means to the transmission medium; and from the transmission medium. A wideband transmission system comprising wideband amplification means for receiving a plurality of transmissions of and providing a plurality of signal outputs that are a function of the received transmissions. 13. The coupling means includes a broadband antenna,
13. The system according to claim 12, wherein the transmission medium is a space surrounding the antenna. 14. A radio receiver for receiving a pulse position modulated wide band signal radiated from a non-resonant transmitting antenna, the discrete electrical receiver receiving a wide band signal from said transmitting antenna and each achieving pulse position modulation. Non-resonant receiving antenna means for providing pulses as output; amplifying means for amplifying a received signal in response to the output of the receiving antenna means; received by the non-resonant receiving antenna having an input for responding to the output of the amplifying means A signal-sensing windowing means responsive to a plurality of signals appearing in a recurring time window, each of which generally corresponds to an averaged pulse generation time, and generating a single output for the plurality of signals, and a reception appearing between the time window occurrences. A synchronous detection means including a dead means that does not sense a signal; an output of the detection means is used to detect an intelligence signal. A radio receiver comprising a signal converting means for converting the signal to a manufactured signal; and a signal reproducing means for reproducing an intelligence signal in response to an output of the signal converting means. 15. The synchronous detection means comprises an avalanche transistor having a signal input connected to the output of the amplification means, the avalanche transistor receiving the input of the avalanche transistor in response to a rising edge of its signal output. 15. A radio receiver as claimed in claim 14, including unregulated gate means for disabling for a selected time period between the recurring time windows. 16. A synchronous demodulating means comprising: a ring demodulator means having a gate input, a signal input and a signal output constituting the output of said synchronous detecting means; responsive to an average output of said outputs of said ring demodulator means. And a voltage controlled oscillator means for generating a pulse output at a frequency corresponding to the average output of the outputs of the ring demodulator means; and one of the repeatedly generated time windows in response to the output of the voltage controlled oscillator means. A radio receiver as claimed in claim 14, comprising gating means for providing a gated input signal having a selected duration defining one window to said ring demodulator means. 17. The gating means includes: a monostable multivibrator having an input and an output coupled to the voltage controlled oscillator means; and the output of the monostable multivibrator and the gate input of the ring demodulator means. A radio receiver according to claim 16, comprising a pulse transformer connected in between.