JPH07271379A - Electronic musical instrument - Google Patents

Abstract

PURPOSE:To perform an automatic playing with a smooth portamento by making the interpolation coefficients of a filtering means and the interpolation coefficients of a delaying means coincident when the interpolation coefficients of the filtering means are larger than the interpolation coefficients of the delaying means. CONSTITUTION:In an interpolation coefficent generating section H2, a tone color code TC and a portamento coefficient PRATE are inputted to a tube length interpolation coefficient generating section 14 and the section 14 outputs tube length interpolation coefficients DRATE. The tone color code TC and lead coefficients RRATE are inputted to a reed filter interpolation coefficient generation section 15 and the section 15 outputs reed filter interpolation coefficients RFR. A comparator 16 compares the DRATE and the RFR. A selector 17 does nothing to the RFR if the RFR are smaller than the DRATE and if the RFR are larger than the DRATE, outputs the DRATE to a reed filter frequency interpolation section H1 as interpolation coefficients RFRATE.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an electronic musical instrument for forming a musical tone by operating a model simulating a sounding mechanism of a natural musical instrument.

[0002]

2. Description of the Related Art This type of electronic musical instrument is particularly suitable for forming a musical tone of a wind instrument, and is used for electronically forming a musical tone such as a trumpet or a trombone. This electronic musical instrument is composed of an excitation circuit that has a filter circuit and a non-linear circuit to simulate the operation of a mouthpiece section, and a loop circuit that has a delay circuit and a filter circuit to simulate the operation of a resonance tube. . Then, the pitch (pitch) of the generated musical sound is determined based on the correlation between the resonance frequency of the filter circuit in the excitation circuit and the resonance frequency of the loop circuit.

[0003]

There is a performance method called portamento. This playing method is a playing method in which the pitches from the first musical tone to the second musical tone are shifted while sequentially producing intervals. In a conventional electronic musical instrument, when playing this portamento automatically, an interpolation coefficient corresponding to the portamento time is set in the interpolation coefficient register, and the delay time of the delay circuit is sequentially changed based on this interpolation coefficient. The resonance frequency was changed to sequentially change the pitch of the generated musical sound. However, since the conventional electronic musical instrument did not interpolate up to the time constant of the filter of the excitation circuit during this portamento performance, the resonance frequency of the loop circuit and the resonance frequency of the excitation circuit filter match during portamento performance. There was a situation where it did not.

FIGS. 9A to 9C show characteristics of the resonance frequency of the loop circuit during the portamento performance (symbol A),
It is a figure showing a filter characteristic (symbol B) of an excitation circuit,
(A) shows the portamento start time, (B) shows a certain time during portamento, and (C) shows the portamento end time. As is clear from these figures, there was a state where the resonance frequency of the loop circuit and the resonance frequency of the filter of the excitation circuit did not match at the midpoint of portamento. When such a situation occurs, there is a problem that the pronunciation becomes very unstable, the sound becomes dull or flipped, and smooth portamento performance cannot be performed.

Further, in the conventional electronic musical instrument, since only a constant interpolation coefficient can be set in the interpolation coefficient register used during portamento performance, noise is generated when the pitches of the first and second musical tones change greatly. There was a problem that arises.

[0006] The present invention has been made under such a background, and an object thereof is to provide an electronic musical instrument capable of performing smooth automatic performance of portamento.

[0007]

The invention according to claim 1 is
An electronic musical instrument for forming a musical tone signal by applying an output signal of an excitation means having a second filter means and a non-linear means to a signal transmission means including a delay means and a first filter means, and an interpolation coefficient of the delay means. , An interpolation coefficient of the second filter means and the interpolation coefficient of the second filter means, in an electronic musical instrument having a function of shifting from the first musical sound to the second musical sound while sequentially generating the interval between them. The comparison means for comparing the interpolation coefficient of the delay means with the comparison means, and as a result of the comparison by the comparison means, if the interpolation coefficient of the second filter means is larger than the interpolation coefficient of the delay means, the second
A means for matching the interpolation coefficient of the filter means with the interpolation coefficient of the delay means is provided.

According to a second aspect of the present invention, a tone signal is formed by applying the output signal of the excitation means having the second filter means and the non-linear means to the signal transmission means including the delay means and the first filter means. An electronic musical instrument having a function of shifting from a first musical tone to a second musical tone while sequentially producing a pitch between the first musical tone and the second musical tone, based on the interpolation coefficient of the delay means and the interpolation coefficient of the second filter means. In the musical instrument, the interpolation coefficient of the delay means is set to a value corresponding to the pitch difference between the first and second musical tones.

[0009]

According to a first aspect of the present invention, the interpolation coefficient of the second filter means is compared with the interpolation coefficient of the delay means, and when the interpolation coefficient of the second filter means is larger than the interpolation coefficient of the delay means, (2) The interpolation coefficient of the filter means is made to match the interpolation coefficient of the delay means. As a result, the changing speed of the resonance frequency of the second filter means is equal to or slower than the changing speed of the resonance frequency of the loop circuit including the exciting means and the signal transmitting means, and as a result, stable portamento performance can be performed. it can.

According to the second aspect of the invention, the interpolation coefficient of the delay means is set to a value corresponding to the pitch difference between the first and second musical tones. As a result, stable portamento performance can be performed even when the pitch difference between the first and second musical tones is large.

[0011]

Embodiments of the present invention will be described below with reference to the drawings. <First Embodiment> FIG. 1 is a block diagram showing the arrangement of an electronic musical instrument according to the first embodiment of the present invention. First, the musical sound synthesizer 18 in this figure will be described, and then the entire description will be given.

A: Structure of Musical Sound Synthesizing Unit 18 FIG. 2 is a block diagram showing the structure of the musical sound synthesizing unit 18.
In this figure, B1 is an excitation circuit, which is a circuit simulating the movement of a mouthpiece (lead) of a wind instrument. Further, B3 and B4 are signal transmission circuits simulating a resonance tube of a wind instrument. Here, the signal transmission circuit B
3 and B4 each simulate a separate resonance tube.
That is, this embodiment simulates a wind instrument having two resonance tubes. B2 is a synthesizing circuit for synthesizing the signals of the excitation unit B1, the signal transmission circuits B3 and B4. B5 is a junction circuit that simulates the tone hole of a wind instrument.

Next, in the excitation circuit B1, the adder A3
Adds the breath pressure information PRES indicating the breath pressure and the signal S1 indicating the pressure of the air vibration wave returned from the tube to the mouthpiece, and outputs the addition result to the lead RF filter 20. The reed RF filter 20 is a low-pass filter that simulates the frequency characteristic of the reed, and its characteristic is determined by the cutoff frequency f0 and the selectivity information Q supplied from the outside. The output of the filter 20 is supplied to the adder A4. The adder A4 outputs the output of the read RF filter 20 and the embouchure information E supplied from the outside.
MB is added, and the addition result is output. Here, the Ambuscheur information is the posture of the lips when playing a wind instrument,
This is information indicating tightening and the like. Reference numerals 21 and 22 are non-linear circuits (ROM) that convert their inputs with non-linear characteristics,
The output of the adder A4 is input together, and the conversion result is multiplied by the multiplier M2.
Output to. Here, each of the nonlinear circuits 21 and 22 is a circuit that simulates the characteristic of the bending (displacement amount) with respect to the external force of the lead and the characteristic of the flow velocity with respect to the differential pressure in the mouthpiece. The multiplier M2 multiplies the outputs of the nonlinear circuits 21 and 22 and outputs the multiplication result to the synthesis circuit B2.

Next, in the synthesis circuit B2, the adder A5
Outputs the outputs of the excitation circuit B1 and the adder A9 (described later), and outputs the addition result to the adders A6, A7 and A8. The adder A6 adds the outputs of the adders A5 and A9 and outputs the addition result as the above-mentioned signal S1.
Output to 1. The adder A7 adds the output of the signal transmission circuit B3 and the output of the adder A5, supplies the addition result to the signal transmission circuit B4, and outputs it as a tone signal OUT to the outside. The adder A8 adds the output of the adder A5 and the output of the signal transmission circuit B4, and outputs the addition result to the signal transmission circuit B3. Further, the adder A9 adds the outputs of the signal transmission circuits B3 and B4 and outputs the addition result to the adder A5.
And output to A6.

As a result, the output of the excitation circuit B1 is B1
→ A5 → A7 → B4 → A9 → A6 → B1 loop at the same time, B1 → A5 → A8 → B3 → A9 → A6 →
The loop is made in the path B1 and a composite signal of these two loop signals is output as the musical tone signal OUT.

The signal transmission circuit B3 comprises a delay circuit 23, a low pass filter 24 and a multiplier M3 connected in series. Here, the delay circuit 23 is a circuit for delaying its input according to the pipe length correction coefficient DRATE, the crossfade start signal XFST, the delay data DL1 and P-DL1 supplied from the outside, and the details thereof will be described later. The low-pass filter 24 has a characteristic determined by the cut-off frequency LPFC1 supplied from the outside, and the reactor wave of its input is applied. Further, the multiplier M3 multiplies its input by the coefficient LG1 supplied from the outside, and outputs the multiplication result. Here, the delay circuit 23 simulates the air flow in the resonance tube, and the low pass filter 24 and the multiplier M3 simulate the end portion of the resonance tube.

FIG. 3 is a block diagram of the delay circuit 23.
In the figure, reference numeral 30 denotes a delay unit, which is, for example, a 16-bit n-stage shift register formed by a flip-flop (FF) and outputs of each stage selected and output according to delay data DL1 and P-DL1. 2 selection circuits.

The delay data DL1 is composed of an integer part D1 and a decimal part d1, and the first selection circuit has an integer part D1.
Make a selection based on 1. Similarly, the delay data DL2 includes an integer part D2 and a decimal part d2, and the second selection circuit makes a selection based on the integer part D2. The data of the stage selected by the first selection circuit is output from the output terminal F1, and the data of the next stage of the same stage is output from the output terminal F1 + 1. Similarly, the data of the stage selected by the second selection circuit is output from the output terminal F2, and the data of the next stage of the same stage is output from the output terminal F2 + 1.

Reference numeral 31 is a decimal part processing circuit, which is a circuit for obtaining the delay corresponding to the decimal part d1 of the delay data DL1 by linear interpolation. In the decimal part processing circuit 31, M8 is a multiplier for multiplying the data at the output terminal F1 by the decimal part d1, M7 is a multiplier for multiplying the decimal part d1 by -1, and A13 is +1 for the output of the multiplier M7. An adder for adding, M9 is a multiplier for multiplying the output terminal F1 + 1 with the output of the adder A13, and A14 is an adder for adding the output of the multiplier M8 to the output of the multiplier M9.

Then, for example, when d1 = 0.2, "0.2" is directly supplied to the multiplier M8 as a multiplication coefficient. Further, the fractional part d1 is multiplied by -1 in the multiplier M7 and further added with "1" in the adder A13, resulting in "0.8" (1-d1), which is supplied to the multiplier A9 as a multiplication coefficient. . The multipliers M8 and M9 multiply the above multiplication coefficient and the data of the output terminals F1 and F1 + 1, and output the multiplication results to the adder A13, respectively. The adder A14 adds the outputs of the multipliers M8 and M9 and outputs the addition result. As a result, "0.
The data delayed by 2 "is output from the adder A14.

Reference numeral 32 is a fractional part processing circuit having the same configuration as the fractional part processing circuit 31 described above, and the delay data DL
This is a circuit for obtaining the delay corresponding to the fractional part d2 of 2 by linear interpolation.

Reference numeral 33 is a crossfade control circuit. The crossfade control circuit 33 always outputs the output of the fractional part processing circuit 31 as output data OUT1 and supplies it to the low-pass filter 24 of FIG. When the crossfade start signal XFST rises to "1", first, the output data OUT1 becomes the same data as the output of the decimal part processing circuit 32, and thereafter, the output data OU
T1 gradually changes toward the output data value of the decimal part processing circuit 31. Then, after a predetermined time, the output data OUT1 becomes the same as the output data of the fractional part processing circuit 31.

In the crossfade control circuit 33, 34 is a crossfade signal generating circuit, which is shown in FIG.
It is a circuit having the characteristics shown in (b). In FIG.
(A) shows the waveform of the crossfade start signal XFST, and (b) shows the waveform of the output crossfade signal XFD. As shown in the figure, the crossfade signal XFD is always "1", but when the crossfade start signal XFST becomes "1", it becomes "0", and then increases exponentially to "1". Go. The rate of increase is determined by the pipe length interpolation coefficient DRATE, and the rate of increase of the signal XFD increases as the tube length interpolation coefficient DRATE increases (see the broken line in FIG. 4B). The crossfade signal XFD is supplied to the multiplier M15, the signal XFD is multiplied by -1 in the multiplier M13, and "1" is added in the adder A17, and then the multiplier M1 is added.
4 is supplied. That is, the multiplication coefficient supplied to the multiplier M14 is normally "0", and the crossfade signal XFD
When is sequentially increased from “0” to “1”, conversely, it is gradually decreased from “1” to “0”. The adder A18 is a multiplier M1
4, the output of M15 is added, and the result of the addition is added to the delay circuit 2
3 as output data OUT1.

Next, in the signal transmission circuit B4 of FIG.
Reference numeral 25 is a delay circuit having the same configuration as the above-mentioned delay circuit 23, and includes delay data DL2, P-DL2, and pipe length interpolation coefficient DR.
The output signal of the combining circuit B2 is delayed according to ATE and the crossfade start signal XDST, and the delay result is output to the junction B5.

At the junction B5, the delay circuit 2
The output of 5 is supplied to the multiplier M4 and the subtractor A10. The multiplier M4 multiplies the output of the delay circuit 25 by the tone Hall coefficient TH1 supplied from the outside, and outputs the multiplication result to the adder A11. The subtractor A10 is the adder A
The output of the delay circuit 25 is subtracted from the output of 11, and the subtraction result is supplied to the synthesis circuit B2 as the output of the signal transmission circuit B4. The other input S2 of the junction B5 is
It is supplied to the subtractor A12 and the multiplier M5. Multiplier M
Reference numeral 5 multiplies the signal S2 by a tone Hall coefficient TH2 supplied from the outside, and outputs the multiplication result to the adder A11. The adder A11 adds the outputs of the multipliers M4 and M5 and outputs the addition result to the subtracters A10 and A12.
The subtractor A12 outputs the signal S2 from the output of the adder A11.
Is subtracted and the result is output to the delay circuit 26.

The delay circuit 26 is the delay circuits 23 and 2 described above.
5 is a delay circuit having the same configuration as that of delay data DL3, P3.
The input is delayed according to -DL3, the pipe length interpolation coefficient DRATE, and the crossfade start signal XDST, and the result is supplied to the low-pass filter 27. The low-pass filter 27 has a characteristic determined by the cut-off frequency LPFC2 supplied from the outside, performs a reactor wave of its input, and supplies the result to the multiplier M6. Also,
The multiplier M6 has its input and the coefficient LG2 supplied from the outside.
And are multiplied, and the multiplication result is output to junction B5 as signal S2. Here, the low-pass filter 27 and the multiplier M6 simulate the end of the tube simulated by the signal transmission circuit B4.

B: Overall Configuration Next, an overall description will be given. In FIG. 1, reference numeral 1 is a performance operator, and a sounding instruction is given by a keyboard or the like. A tone color setting operator 2 is used to set tone colors such as the type of wind instrument and portamento. Reference numeral 3 denotes a control unit which, based on the outputs of the performance operator 1 and the tone color setting operator 2, outputs a key code KC, a key-on signal KON, a tone color code TC, breath pressure information PRES, embouchure information EMB, and portamento information PON. Output. Here, the key-on signal KON is "when the keyboard key of the performance operator 1 is turned on."
It is a signal which becomes "1" and becomes "0" when turned off.
Further, the portamento information PON indicates whether portamento is valid or invalid, and outputs “1” when valid and outputs “0” when invalid. Also, breath pressure information PRES,
The embouchure information EMB is directly supplied to the excitation circuit B1 (FIG. 2) of the musical sound synthesizer 18.

Reference numeral 4 in FIG. 1 denotes a pitch control data generator, which inputs a key code KC, and based on this data, total delay TD and tone hole opening / closing information OP.
S, cutoff frequency RFf0 is output. Here, the total delay TD is data indicating the total delay time of each loop circuit of the musical sound synthesizer 18, and the tone hole opening / closing information OPS is data indicating the opening / closing state of the tone hole corresponding to the pitch. Also, the cutoff frequency RFf
0 is the cutoff frequency of the lead RF filter 20.

Reference numerals 5 and 6 respectively denote a latch, which is a total delay TD supplied from the pitch control data generator 4.
Then, the key code KC supplied from the control unit 3 is input, and each input is latched (held) at the rising edge of the key-on signal KON also supplied from the control unit 3.
Then, the latch 5 outputs the latch result as a pre-total delay P-TD, and the latch 6 outputs the latch result as a pre-key code P-KC.

The delay distributor 7 is composed of a ROM, and the total delay TD output from the pitch control data generator 4 and the output pre-total delay P-TD of the latch 5 which is the value before the change of the total delay TD. , Input the tone color code TC supplied from the control unit 3,
Delay data DL1, DL2, D based on their inputs
The L3, P-DL1, P-DL2, and P-DL3 are output to the delay circuits 23, 25, and 26 of the musical sound synthesizer 18 described above. Here, the delay data DL1, DL2, and DL3 are determined corresponding to the total delay TD, and the pre-delay data P-DL1 are determined corresponding to the pre-total delay P-TD.
P-DL2 and P-DL3 are determined.

Reference numeral 8 is a tone hole coefficient generator composed of a ROM, which outputs tone hole coefficients TH1 and TH2 corresponding to the tone color code TC and the tone hole opening / closing information OPS.

Reference numeral 9 denotes a comparator, which inputs the key code KC and the pre-key code P-KC output from the latch 6, outputs "0" when these two input values are equal, and does not equal. In that case, "1" is output. The AND gate 10 is supplied with the output of the comparator 9, the key-on signal KON and the portamento signal PON, and each signal is "1".
In the case of, the output can be "1". This output is supplied to the delay circuits 23, 25 and 26 of the musical tone synthesizer 18 as a crossfade start signal XFST.

The crossfade start signal XFST will be further described. Outputs from the control unit 3 when the keyboard keys are sequentially separated and turned on, that is, when one key is turned on and the next key is turned on after the key is turned off Key code KC and pre-key code P output from the latch 6
-KC is always the same, and therefore AND gate 1
The output of 0 is always "0". On the other hand, when the keyboard keys are turned on in duplicate, that is, when the other key is turned on while one key is turned on, the latch 6
Holds the first key code KC, while the controller 3
Outputs the key code KC of the key that was turned on later. As a result, the output of the comparator 9 becomes "1", and when the portamento signal PON is "1", the crossfade start signal XFST rises to "1". That is,
The crossfade start signal XFST becomes "1" when the portamento signal PON is "1" and when the keyboard keys are turned on in duplicate.

The relationship between the total delay TD and the pre-total delay P-TD described above is the same as the relationship between the key code KC and the pre-key code P-KC described above.
That is, when the keyboard keys are sequentially separated and turned on, the total delay TD and the pre-total delay P-TD
And are always the same, and when the keyboard keys are turned on in duplicate, the total delay TD and the pre-total delay P-TD are different data.

12 is a parameter data generator (ROM)
And the portamento coefficient PRATE and the read coefficient RRA based on the tone color code TC supplied from the control unit 3.
TE is output to the interpolation coefficient generator H2. Further, the selectivity information Q, the multiplication coefficients LG1 and LG2, the cutoff frequency LP
The FC1 and the LPFC2 are output to the musical sound synthesizer 18.

The interpolation coefficient generation unit H2 uses the pipe length interpolation coefficient DRA.
TE (see FIG. 3) and read filter interpolation coefficient RFR
This is a circuit that generates ATE. This interpolation coefficient generator H2
In, the gate circuit 13 receives the portamento signal PON output from the controller 3 and the portamento coefficient PRATE output from the parameter data generator 12, and outputs the portamento coefficient PRATE when the portamento signal PON is “1”, Portamento signal PON is
When it is "0", "0" is output.

Reference numeral 14 denotes a pipe length interpolation coefficient generator (ROM) which inputs the output of the gate circuit 10 and the tone color code TC and outputs a pipe length interpolation coefficient DRATE indicating the rate of continuous change of the pipe length during portamento. .

Reference numeral 15 is a read filter interpolation coefficient generator (R
OM), the tone color code TC and the read coefficient RRATE output from the parameter data generator 9 are input,
Cutoff frequency f of the reed RF filter 24 (FIG. 2)
The read filter interpolation coefficient RFR indicating the rate of change of 0 is output. The pipe length interpolation coefficient DRATE and the read filter interpolation coefficient RFR are supplied to the comparator 16, which outputs "1" when the pipe length interpolation coefficient DRATE is smaller than the read filter interpolation coefficient RFR and outputs "0" when it is larger. To do.

Reference numeral 17 denotes a selector which outputs a pipe length interpolation coefficient DRATE when the output of the comparator 16 is "1" and a read filter interpolation coefficient RFR when the output of the comparator 13 is "0". Is output. That is, when the read filter interpolation coefficient RFR is smaller than the tube length interpolation coefficient DRATE, the selector 17 reads the read filter interpolation coefficient R.
FR is output as the interpolation coefficient RFRATE as it is, but the read filter interpolation coefficient RFR is the pipe length interpolation coefficient DR.
When it is larger than ATE, the pipe length interpolation coefficient DRATE is replaced with the interpolation coefficient RFRATE instead of the read filter interpolation coefficient RFR.
Output as.

The reason for such a configuration is as follows. That is, during portamento performance, when the generated musical tone sequentially changes from the first musical tone to the second musical tone, the changing speed of the pipe length (the changing speed of the delay amount of the loop circuit) is determined by the pipe length interpolation coefficient DRATE. The rate of change of the cutoff frequency of the Reed RF filter 20 (FIG. 2) is determined based on the Reed filter interpolation coefficient RFR. By the way, when the change speed of the cutoff frequency of the reed is slower than the change speed of the tube length, there is no problem, but when the change speed is high, the pronunciation becomes unstable and smooth portamento performance cannot be performed. So, configure as above, and by this,
The change rate of the cutoff frequency of the lead does not exceed the change rate of the tube length.

Next, the read filter frequency interpolation unit H1
Is an adder A1, A2, a multiplier M1, and a delay element 1
1 (D-type flip-flop) and performs interpolation when the read filter frequency f0 changes. The adder A1 adds the read filter frequency RFf0 supplied from the pitch control data generator 4 and the output of the delay element 11, and outputs the addition result to the multiplier M1. The multiplier M1 multiplies the output of the adder A1 by the read filter interpolation coefficient RFRATE which is the output of the correction coefficient generator H3, and outputs the multiplication result to the adder A2. The output of the multiplier M1 and the output of the delay element 11 are added to the adder A2, and the addition result is output to the delay element 11. The delay element 11 delays its input by one timing of the system clock φ, and uses the result as a cutoff frequency f0 for the lead R of the tone synthesizer 18.
The data is output to the F filter 20 and fed back to the adders A1 and A2.

In such a configuration, when the read filter frequency RFf0 changes, the cutoff frequency f0 is changed.
According to the read filter interpolation coefficient RFRATE, changes exponentially from the value before the change of the read filter frequency RFf0 to the value after the change.

C: Description of Overall Operation Next, the operation of the above-described electronic musical instrument will be described. First, when a tone color is set by operating the tone color switch in the tone color setting operator 2 (FIG. 1), a tone color code TC corresponding to the set tone color is output from the control unit 3 and supplied to the parameter data generation unit 12. To be done. As a result, various parameters are output from the parameter data generator 12.

Next, it is assumed that the portamento switch in the tone color setting operator 2 is turned off. In this case, the portamento signal PON output from the control unit 3 becomes "0",
Therefore, the crossfade start signal XFST output from the AND gate 10 becomes "0". As a result, the output of the crossfade signal generation circuit 34 of FIG. 3 becomes "1", and thereafter, the output data of the fractional part processing circuit 31 is output from the delay circuit 23 via the multiplier M15.

When the performer operates the keyboard keys of the performance operator 1, the control section 3 causes the key code KC, the key-on signal KON, the embouchure information EMB, and the breath pressure information PR.
ES is output. When the key code KC is output from the control unit 3 and is output to the pitch control data generation unit 4, the pitch control data generation unit 4 outputs the total delay TD corresponding to the key code KC, the tone hole opening / closing information OPS, and the lead filter. The frequency RFf0 is output. As a result, the delay distributor 7 outputs the delay data DL1, DL2, DL3 corresponding to the key code KC, and the tone hole coefficient generator 8 outputs the tone hole coefficients TH1, TH2 corresponding to the key code KC. . The read filter frequency interpolator H1 first outputs the initial data "0", and thereafter outputs the cutoff frequency f0 which sequentially changes up to the read filter frequency RFf0.

Also, the embouchure information E from the control unit 3
MB and breath pressure information PRES are output, and the excitation circuit B1
(Fig. 2), output data is generated in the adder A3 of the excitation circuit B1, and the excitation circuit B is generated based on this data.
1. Circulating musical tone data is generated in each of the loop formed by the synthesizing circuit B2, the signal transmitting circuit B4 and the exciting circuit B1, the synthesizing circuit B2, the signal transmitting circuit B3, and these circulating musical tone data are synthesized. The data is output as tone data OUT. The output musical sound data OUT is converted into an analog signal by a D / A converter (not shown), and a sound system (not shown)
Is supplied to.

Next, when the player turns on the portamento switch, the controller 3 causes the portamento signal P to be output.
ON "1" is output. Portamento signal PON is
When it becomes "1" and this "1" signal is supplied to the AND gate 10, the AND gate 10 becomes active thereafter.
Also, the portamento signal PON "1" is AND gate 1
3, the AND gate 13 is opened, and the portamento coefficient PRATE output from the parameter data generator 12 is supplied to the pipe length interpolation coefficient generator 14 via the AND gate 13. Pipe length interpolation coefficient generator 14
Receives this portamento coefficient PRATE, and outputs a pipe length interpolation coefficient DRATE corresponding to the tone color code TC and also corresponding to the portamento coefficient PRATE.

In this state, if the player duplicately operates the keyboard keys, the crossfade start signal XFS
Crossfade signal XFD output from the crossfade signal generation circuit 34 (FIG. 3) when T rises to "1"
Becomes "0". As a result, the coefficient "1" is supplied to the multiplier M14, and the output of the fractional part processing circuit 32 (the output corresponding to the delay data P-DL1) is output from the delay circuit 23 via the multiplier M14 and the adder A18. To be done.
In this case, the delay data P-DL1 is the delay data of the previous key depression, and therefore, the generated musical tone does not change in the above process. At this time, the delay data DL1 is the delay data for the subsequent key depression.

After that, when the crossfade signal XFD sequentially becomes large in accordance with the exponential function, the delay circuit 23 is accordingly accompanied.
Also, the delay time of is sequentially changed from the delay time corresponding to the delay data P-DL1 to the delay time corresponding to the delay data DL1. Further, at this time, the cutoff frequency f0 supplied to the read RF filter 20 (FIG. 2) also sequentially changes from the data corresponding to the previous key depression to the data corresponding to the subsequent key depression. As a result, the generated musical tone sequentially changes from the musical tone of the previous key depression to the musical tone of the subsequent key depression. When the crossfade signal XFD becomes "1", the generated musical sound becomes the musical sound of the subsequent key depression, and the portamento performance ends.

In the above embodiment, the dimensions of the resonance frequency of the tube and the resonance frequency (cutoff frequency) of the lead do not match for simplification. Therefore, even if the same interpolation coefficient is set, the change rates of the resonance frequency and the cutoff frequency will be different. Therefore, there is a method of using the interpolation coefficient as the frequency so that the dimensions are the same.

The relationship between the tube length l and the resonance frequency fl at this time is: fl = Fs / l (Fs is a sampling frequency) The relationship between the coefficient a of the reed RF filter and the cutoff frequency fc at this time is fc = Fs * a / 2π. The pipe length interpolation coefficient is once converted into a frequency and given to the control unit. The control unit may calculate l = Fs / fl a = 2π * fc / Fs as the pipe length interpolation coefficient and the filter coefficient.

<Second Embodiment> FIG. 5 is a block diagram showing the configuration of the second embodiment of the present invention. In this figure,
Reference numeral 41 is an exciting circuit, and 42 is a combining circuit, which is configured similarly to the exciting circuit B1 and the combining circuit B2 in FIG. Reference numeral 43 is an adder, 44 is a multiplier for multiplying input data by a coefficient α, and 45 is a multiplier for multiplying input data by a coefficient β. Reference numerals 46 and 47 denote signal transmission circuits having the same configuration, respectively, and have the same configuration as the signal transmission circuit B4 in FIG. However, while the signal transmission circuit 46 is supplied with a total delay TD from a control circuit (not shown), the signal transmission circuit 47 is supplied with a pre-total delay P-TD from the control circuit.

Reference numeral 48 is an adder, 49 is a multiplier for multiplying input data by a coefficient α, and 50 is a multiplier for multiplying input data by a coefficient β. Reference numerals 51 and 52 denote signal transmission circuits having the same configuration, respectively. The signal transmission circuit B3 of FIG.
Is configured similarly to. However, also in this case, the signal transmission circuit 51 is supplied with the total delay TD from the control circuit (not shown), while the signal transmission circuit 52 is supplied with the pre-total delay P-TD from the control circuit.

FIG. 6 shows a portamento control section, which is composed of an interpolation coefficient generation circuit 55 for generating interpolation coefficients during portamento performance, and a crossfade signal generation circuit 56. Details of the interpolation coefficient generation circuit 55 are shown in FIG. In this figure, 60 is a subtractor for taking the difference between the key code KC and the pre-key code P-KC, and 61 is the subtractor 60.
An absolute value conversion circuit for taking the absolute value of the output of the reference numeral 62 is a multiplier for multiplying the output of the absolute value conversion circuit 61 by a coefficient k1.

Reference numeral 63 is a subtracter for taking the difference between the total delay TD and the pre-total delay P-TD, 64 is an absolute value conversion circuit for taking the absolute value of the output of the subtractor 63, and 65 is the output of the absolute value conversion circuit 64. This is a multiplier that multiplies the coefficient k2. Reference numeral 66 is an exclusive OR gate, which has tone hole opening / closing information OPS and pre-tone hole opening / closing information P-.
When the OPSs do not match, a "1" signal is output and the AND gate 67 is opened. Here, the pre-tone hole opening / closing information P-OPS is the tone hole opening / closing information corresponding to the previous key depression during portamento performance.

Reference numeral 68 is a correction amount table, and correction data for correcting the crossfade coefficient XFDD described below is stored for each tone color code TC. The correction data in the correction table 68 is output via the AND gate 67 when the tone hole opening / closing information OPS and the pretone hole opening / closing information P-OPS do not match, and is used for correcting the crossfade coefficient XFDD. .

In the crossfade coefficient table 69, the default value of the crossfade coefficient XFDD is the tone color code TC.
It is a table stored for each. The weighting coefficient table 70 is a table in which weighting coefficients k1 and k2 corresponding to the tone color code TC are stored, and the coefficients k1 and k2 read from the table 70 are supplied to the multipliers 62 and 65, respectively.

An adder 72 adds the outputs of the multipliers 62 and 65 and outputs the addition result to the adder 73. The adder 73 adds the correction data output from the AND gate 67 to the output of the adder 72, and outputs the result to the adder 74. The adder 74 adds the crossfade coefficient XFDD and the output of the adder 73, and the result is added to the pipe length interpolation coefficient D.
It is output as RATE to the crossfade signal generation circuit 56 (FIG. 6).

According to such a configuration, the crossfade coefficient XFDD is determined by the key code KC and the pre-key code P-.
According to the difference between KC and the difference between the total delay TD and the pre-total delay P-TD,
The tone hole opening / closing information OPS and the pretone hole opening / closing information P-OPS are corrected depending on whether they match, and the corrected result is output as the pipe length interpolation coefficient DRATE.

Next, the crossfade signal generating circuit 56 of FIG. 6 is a circuit for generating the multiplication coefficients α and β of FIG.
When the crossfade start signal XFST is "0", α
= 1 and β = 0 are output, and the crossfade start signal X is output.
When FST rises to "1", thereafter, as shown in FIG. 8, a coefficient α gradually increases from "0" to "1" and a coefficient β gradually decreases from "1" to "0". Generate a coefficient. Then, in this case, the rising and falling slopes have the above-described pipe length interpolation coefficient DRA.
Determined by TE.

In the above configuration, normally, α = 1, β
Since = 0, the signal transmission circuits 46 and 51 form a loop circuit together with the excitation circuit 41 and the synthesis circuit 42, and the tone formation is performed by this loop circuit. On the other hand, when the portamento switch is turned on and the keyboard keys are duplicated, the crossfade start signal XFST
Rises to "1". As a result, α = 0 and β = 1, and the musical tone of the previous key depression is formed in the signal transmission circuits 47 and 52. Thereafter, the musical tone formation subject is sequentially the signal transmission circuit at a speed according to the pipe length interpolation coefficient DRATE. Move to 46, 51. As a result, the generated musical tones are sequentially transferred to the musical tones based on the subsequent key depression. Then, when α = 1 and β = 0, thereafter, in the signal transmission circuits 46 and 51, a musical tone based on the subsequent key depression is formed.

[0062]

As described above, according to the present invention, the interpolation coefficient of the filter means included in the excitation means is compared with the interpolation coefficient of the delay means included in the signal transmission means, and the interpolation coefficient of the filter means is compared to the delay means. If it is larger than the interpolation coefficient of, the interpolation coefficient of the filter means is made to match the interpolation coefficient of the delay means. As a result, the changing speed of the resonance frequency of the filter means is equal to or slower than the changing speed of the resonance frequency of the loop circuit including the exciting means and the signal transmitting means, and as a result, stable portamento performance can be performed.

Further, according to the present invention, the interpolation coefficient of the delay means is set to a value corresponding to the pitch difference between the first and second musical tones. As a result, it is possible to obtain a stable portamento performance even when the pitch difference between the first and second musical tones is large.

[Brief description of drawings]

FIG. 1 is a block diagram showing the configuration of a musical sound synthesizer according to a first embodiment of the present invention.

FIG. 2 is a block diagram showing a configuration of a musical tone synthesis section 18 of FIG.

3 is a block diagram showing a configuration of a delay circuit 23 of FIG.

FIG. 4 is a waveform diagram showing input / output signals of the crossfade signal generating circuit of FIG.

FIG. 5 is a block diagram showing the structure of a musical sound synthesizer according to a second embodiment of the present invention.

6 is a block diagram showing a configuration of a portamento control unit in FIG.

7 is a block diagram showing a configuration of an interpolation coefficient generator 55 of FIG.

FIG. 8 is a diagram showing how the multiplication coefficients α and β in FIG. 6 change.

FIG. 9 is a diagram showing a resonance frequency characteristic (symbol A) of a loop circuit and a filter characteristic (symbol B) of an excitation circuit in a conventional portamento performance, in which (a) is a portamento start time point and (b) is a portamento. At some point in the middle, (c) indicates the end point of portamento.

[Explanation of symbols]

 1 Performance Operator 2 Tone Setting Operator 3 Control Section 4 Pitch Control Data Generation Section 5, 6 Latch 7 Delay Distributor 8 Tone Hall Coefficient Generator 9, 17 Comparator 11 Delay Element 12 Parameter Data Generator 14 Pipe Length Interpolation Coefficient Generator 15 Lead filter interpolation coefficient generator 17 Switcher 18 Musical sound synthesizer H1 Lead filter frequency interpolator H2 Interpolation coefficient generator B1 Excitation circuit B2 Synthesis circuit B3, B4 Signal transmission circuit B5 Junction 30 Delay unit 33 Crossfade control circuit

Claims (2)

[Claims] 1. An electronic musical instrument for forming a musical tone signal by applying an output signal of an excitation means having a second filter means and a non-linear means to a signal transmission means including a delay means and a first filter means, wherein the delay is provided. An electronic musical instrument having a function of sequentially shifting a pitch from a first musical tone to a second musical tone while successively producing a pitch based on the interpolation coefficient of the second filtering means and the interpolation coefficient of the second filtering means. Comparing means for comparing the interpolation coefficient of the delay means with the interpolation coefficient of the delay means, and when the interpolation coefficient of the second filter means is larger than the interpolation coefficient of the delay means as a result of the comparison by the comparing means, 2) An electronic musical instrument comprising: a means for matching the interpolation coefficient of the filter means with the interpolation coefficient of the delay means. 2. An electronic musical instrument for forming a musical tone signal by applying an output signal of an excitation means having a second filter means and a non-linear means to a signal transmission means including a delay means and a first filter means, wherein the delay is provided. In the electronic musical instrument having the function of shifting from the first musical tone to the second musical tone while successively producing the pitch between the first musical tone and the second musical tone based on the interpolation coefficient of the delaying means and the interpolation coefficient of the second filtering means, the interpolation of the delaying means An electronic musical instrument, wherein a coefficient is a value corresponding to a pitch difference between the first and second musical tones.