JPH06343044A - Reference voltage generating circuit - Google Patents

Reference voltage generating circuit

Info

Publication number
JPH06343044A
JPH06343044A JP13042993A JP13042993A JPH06343044A JP H06343044 A JPH06343044 A JP H06343044A JP 13042993 A JP13042993 A JP 13042993A JP 13042993 A JP13042993 A JP 13042993A JP H06343044 A JPH06343044 A JP H06343044A
Authority
JP
Japan
Prior art keywords
current
transistor
emitter
circuit
detection
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
JP13042993A
Other languages
Japanese (ja)
Inventor
Kenichi Tatehara
健一 田手原
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Panasonic Holdings Corp
Original Assignee
Matsushita Electric Industrial Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Matsushita Electric Industrial Co Ltd filed Critical Matsushita Electric Industrial Co Ltd
Priority to JP13042993A priority Critical patent/JPH06343044A/en
Publication of JPH06343044A publication Critical patent/JPH06343044A/en
Pending legal-status Critical Current

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  • Amplifiers (AREA)
  • Analogue/Digital Conversion (AREA)

Abstract

PURPOSE:To accurately apply the differential input voltage to both ends of a reference resistor array. CONSTITUTION:An emitter follower circuit 28 includes a series circuit of resistors 3a-3d connected between the emitter outputs of an emitter follower resistor TR 2 whose base is connected to an input terminal 9 and an emitter follower TR 4 whose base is connected to an input terminal 8. A current detecting circuit 29 generates the output currents in response to the output potentials of the emitters of both TR 2 and 4 and also generates a detection output current that is defined by subtracting a 2nd detection current of smaller value from a 1st detection current of larger value. A current compensating circuit 30 generates both positive and negative polar compensating currents based on the detection output current generated by the circuit 29 and then applies these compensating currents to both ends of the series circuit of resistors 3a-3d. In such a constitution, the operating currents of both TR 2 and 4 are never affected by the differential input voltage and the reference voltage can be divided with high accuracy.

Description

【発明の詳細な説明】Detailed Description of the Invention

【0001】[0001]

【産業上の利用分野】この発明は、直並列型A/Dコン
バータの基準電圧発生回路に関するものである。
BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a reference voltage generating circuit for a serial / parallel A / D converter.

【0002】[0002]

【従来の技術】近年、A/Dコンバータは、従来全並列
型のA/Dコンバータが主流であったが、消費電力を低
減することやチップサイズを低減するために、直並列型
のA/Dコンバータが主流に変わってきた。そして、ア
ナログ信号をディジタル信号に変換する際に、基準電圧
に対するアナログ信号の入力の手段が問題となり、様々
な方法が提案されている。
2. Description of the Related Art Recently, all-parallel A / D converters have been the mainstream of A / D converters in recent years. However, in order to reduce power consumption and chip size, serial / parallel A / D converters are used. D converters have become the mainstream. When converting an analog signal into a digital signal, a means for inputting the analog signal to the reference voltage becomes a problem, and various methods have been proposed.

【0003】以下に従来の基準電圧発生回路について説
明する。図2は、アナログ信号の入力手段である従来の
基準電圧発生回路の一例の回路図である。図において、
1は第1の定電位、2および4はトランジスタ、3a,
3b,3c,3dは抵抗値Rの抵抗、5および6は電流
値I0 の定電流源、7は第2の定電位、8は第2の入力
端子、9は第1の入力端子である。
A conventional reference voltage generating circuit will be described below. FIG. 2 is a circuit diagram of an example of a conventional reference voltage generating circuit that is an analog signal input means. In the figure,
1 is a first constant potential, 2 and 4 are transistors, 3a,
3b, 3c, 3d are resistors having a resistance value R, 5 and 6 are constant current sources having a current value I 0 , 7 is a second constant potential, 8 is a second input terminal, and 9 is a first input terminal. .

【0004】そして、従来の基準電圧発生回路は、トラ
ンジスタ2および4はエミッタ回路の各々に電流源5お
よび6が接続されたエミッタホロワ用のトランジスタで
あり、そのエミッタ出力間に抵抗3a〜3dが直列接続
され、入力端子8と9間に差動の入力信号が入力される
構成である。このように構成された基準電圧発生回路に
ついて、以下その動作を説明する。まず、第1の入力端
子9に入力電圧VIHを入力し、第2の入力端子8にVIH
より低い入力電圧VILを入力する。つぎに、基準抵抗3
aの上端にはトランジスタ2のベース・エミッタ間電圧
をVBE1 とするとVIH−VBE1 なる電圧が印加され、基
準抵抗3dの下端にはトランジスタ4のベースエミッタ
間電圧をVBE2 とするとVIL−VBE2 なる電圧が印加さ
れる。よって基準抵抗列の両端にはVIH−VILなる電圧
が印加されることになる。この印加電圧をもとにして最
終段の変換を行う。
In the conventional reference voltage generating circuit, the transistors 2 and 4 are emitter follower transistors in which the current sources 5 and 6 are connected to the respective emitter circuits, and resistors 3a to 3d are connected in series between the emitter outputs. It is connected and a differential input signal is input between the input terminals 8 and 9. The operation of the reference voltage generating circuit thus configured will be described below. First, the first input terminal 9 receives the input voltage V the IH, V the IH to the second input terminal 8
Input a lower input voltage V IL . Next, the reference resistance 3
When the base-emitter voltage of the transistor 2 is V BE1 , a voltage V IH −V BE1 is applied to the upper end of a, and when the base-emitter voltage of the transistor 4 is V BE2 , V IL is applied to the lower end of the reference resistor 3 d. A voltage of −V BE2 is applied. Therefore V the IH -V IL becomes voltage is to be applied to both ends of the reference resistor string. The final stage conversion is performed based on this applied voltage.

【0005】[0005]

【発明が解決しようとする課題】しかしながら上記の従
来の構成では、基準抵抗列に(VIH−VIL)/4Rなる
基準電流Irが流れる。よって、トランジスタ2のエミ
ッタ電流IE1は、I0 +(VIH−VIL)/4Rとなる。
一方トランジスタ4のエミッタ電流IE2はI0 −(VIH
−VIL)/4Rとなる。この電流差によってVBE1 とV
BE2 に差が発生し差動入力電圧VIH−VILが正確に基準
抵抗列の両端に印加されないという欠点を有していた。
In the [0005] However the conventional structure described above, the reference resistor string (V IH -V IL) / 4R becomes the reference current Ir flows. Therefore, the emitter current I E1 of the transistor 2 becomes I 0 + (V IH −V IL ) / 4R.
On the other hand, the emitter current I E2 of the transistor 4 is I 0 − (V IH
-V IL ) / 4R. This current difference causes V BE1 and V
It has a drawback that a difference occurs in BE2 and the differential input voltage V IH -V IL is not accurately applied across the reference resistor string.

【0006】この発明は上記従来の問題点を解決するも
ので、差動入力電圧VIH−VILを正確に基準抵抗列の両
端に印加することのできる基準電圧発生回路を提供する
ことを目的とする。
The present invention solves the above-mentioned conventional problems, and an object of the present invention is to provide a reference voltage generating circuit capable of accurately applying a differential input voltage V IH -V IL across the reference resistor string. And

【0007】[0007]

【課題を解決するための手段】この発明の基準電圧発生
回路は、エミッタホロワ回路と電流検出回路と電流補償
回路とを備えている。エミッタホロワ回路は、第1の入
力端子がベースに接続されたエミッタホロワ用の第1の
トランジスタと、第2の入力端子がベースに接続された
エミッタホロワ用の第2のトランジスタと、第1,第2
のトランジスタのエミッタ間に直列接続された複数の抵
抗とからなる。
A reference voltage generating circuit according to the present invention comprises an emitter follower circuit, a current detecting circuit and a current compensating circuit. The emitter follower circuit includes a first transistor for an emitter follower having a first input terminal connected to a base, a second transistor for an emitter follower having a second input terminal connected to a base, and first and second
And a plurality of resistors connected in series between the emitters of the transistors.

【0008】電流検出回路は、第1,第2のトランジス
タの各エミッタに入力端が接続され、エミッタの各電位
に応じた検出電流を発生するとともに電流値の大きい第
1の検出電流から電流値の小さい第2の検出電流を差し
引いた検出出力電流を発生する。電流補償回路は、電流
検出回路の検出出力電流を入力とし、検出出力電流を正
極性と負極性の補償電流に変換して、正極性の補償電流
を第1のトランジスタのエミッタに供給し、かつ負極性
の補償電流を第2のトランジスタのエミッタに供給す
る。
The current detection circuit has an input terminal connected to each emitter of the first and second transistors, generates a detection current according to each potential of the emitter, and outputs a current value from the first detection current having a large current value. To generate a detection output current from which the second detection current having a small value is subtracted. The current compensation circuit receives the detection output current of the current detection circuit as input, converts the detection output current into positive and negative compensation currents, and supplies the positive compensation current to the emitter of the first transistor, and A negative compensating current is supplied to the emitter of the second transistor.

【0009】[0009]

【作用】この発明の基準電圧発生回路は、上記の構成に
よって、高い入力インピーダンスを確保するとともに、
差動のエミッタ出力電位に応じた電流が電流検出回路で
検出され、その検出電流の電流値の正負が抵抗列の両端
に供給されるため、エミッタホロワ用の各トランジスタ
の動作電流が入力電圧の大きさの如何に関わらず一定に
なり、エミッタホロワ用トランジスタの入出力間の非線
形特性の影響が無くなり、差動入力電圧VIH−VILが基
準抵抗列の両端に正確に印加できる。
The reference voltage generating circuit of the present invention ensures a high input impedance and has the above-mentioned configuration.
A current according to the differential emitter output potential is detected by the current detection circuit, and the positive / negative of the detected current value is supplied to both ends of the resistor string.Therefore, the operating current of each transistor for the emitter follower is larger than the input voltage. It becomes constant irrespective of the situation, the influence of the nonlinear characteristic between the input and output of the emitter follower transistor is eliminated, and the differential input voltage V IH −V IL can be accurately applied to both ends of the reference resistor string.

【0010】[0010]

【実施例】以下この発明の一実施例について、図面を参
照しながら説明する。図1はこの発明の一実施例におけ
る2ビットの変換を行う場合の基準電圧発生回路の回路
図を示すものである。図1において、1は第1の定電
位、2は第1のNPNトランジスタ、3a,3b,3
c,3dは抵抗値Rの基準抵抗、4は第2のNPNトラ
ンジスタ、5は電流値I0 の第1の定電流回路、6は電
流値I0 の第2の定電流回路、7は第2の定電位、8は
第2の入力端子、9は第1の入力端子である。
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS An embodiment of the present invention will be described below with reference to the drawings. FIG. 1 is a circuit diagram of a reference voltage generating circuit in the case of performing 2-bit conversion according to an embodiment of the present invention. In FIG. 1, 1 is a first constant potential, 2 is a first NPN transistor, 3a, 3b, 3
c, 3d is the reference resistance of the resistance value R, the second NPN transistor 4, the first constant current circuit of the current value I 0 5, the second constant current circuit of the current value I 0 6, 7 first 2 is a constant potential, 8 is a second input terminal, and 9 is a first input terminal.

【0011】10は第1の抵抗、11は第1のPNPト
ランジスタ、12は第3のNPNトランジスタ、13は
抵抗値4Rの第2の抵抗、14は第3の抵抗、15は第
2のPNPトランジスタ、16は第4のNPNトランジ
スタ、17は抵抗値4Rの第4の抵抗である。18は第
5の抵抗、19は第3のPNPトランジスタ、20は第
6のNPNトランジスタ、21は第9の抵抗、22は第
6の抵抗、23は第4のPNPトランジスタ、24は第
7の抵抗、25は第5のPNPトランジスタ、26は第
5のNPNトランジスタ、27は第8の抵抗である。
Reference numeral 10 is a first resistor, 11 is a first PNP transistor, 12 is a third NPN transistor, 13 is a second resistor having a resistance value of 4R, 14 is a third resistor, and 15 is a second PNP. A transistor, 16 is a fourth NPN transistor, and 17 is a fourth resistor having a resistance value of 4R. 18 is a fifth resistor, 19 is a third PNP transistor, 20 is a sixth NPN transistor, 21 is a ninth resistor, 22 is a sixth resistor, 23 is a fourth PNP transistor, and 24 is a seventh resistor. A resistor, 25 is a fifth PNP transistor, 26 is a fifth NPN transistor, and 27 is an eighth resistor.

【0012】28はエミッタホロワ回路、29は電流検
出回路、30は電流補償回路である。以上のように構成
されたこの実施例の基準電圧発生回路について、以下そ
の動作を説明する。まず第1の入力端子9にVIHなる入
力電圧が印加されると、トランジスタ16のエミッタの
電位はVIH−2VBEとなるので、トランジスタ16のコ
レクタ電流IC16 は(VIH−2VBE)/4Rとなる。つ
ぎに、第2の入力端子8にVILなる入力電圧が印加され
ると、トランジスタ12のエミッタの電位はV IL−2V
BEとなるので、トランジスタ12のコレクタ電流IC12
は(VIL−2V BE)/4Rとなる。
28 is an emitter follower circuit and 29 is a current detector.
The output circuit, 30 is a current compensation circuit. Configured as above
The reference voltage generation circuit of this embodiment, which has been
The operation of will be described. First, V is applied to the first input terminal 9.IHNaruiri
When a force voltage is applied, the emitter of transistor 16
Potential is VIH-2VBETherefore, the transistor 16
Rector current IC16Is (VIH-2VBE) / 4R. One
The V input to the second input terminal 8.ILInput voltage is applied
Then, the potential of the emitter of the transistor 12 is V IL-2V
BETherefore, the collector current I of the transistor 12 isC12
Is (VIL-2V BE) / 4R.

【0013】つぎに、電流IC12 をトランジスタ11,
トランジスタ12,抵抗14,トランジスタ15によっ
て電流方向を逆にすることにより、電流IC16 との差電
流がトランジスタ19のコレクタ電流IC19 となる。こ
の電流IC19 をトランジスタ23と抵抗22で電流方向
を逆にしてトランジスタ2のエミッタ端子に流入させる
ことにより、基準抵抗列に流出する電流を補償すること
が可能となる。
Next, the current I C12 is applied to the transistor 11,
By reversing the current direction by the transistor 12, the resistor 14, and the transistor 15, the difference current from the current I C16 becomes the collector current I C19 of the transistor 19. By causing the current I C19 to flow in the emitter terminal of the transistor 2 with the current directions reversed by the transistor 23 and the resistor 22, it is possible to compensate the current flowing out to the reference resistor string.

【0014】つぎに、電流IC19 をトランジスタ25,
トランジスタ26,トランジスタ20,抵抗24,抵抗
27,抵抗21によって電流方向を逆にしてトランジス
タ4のエミッタ端子から吹出すことにより、基準抵抗列
から流入する電流を補償することが可能となる。この電
流補償を行うことによって差動入力電圧VIH−VILを正
確に基準抵抗列の両端に印加することができる。
Next, the current I C19 is supplied to the transistor 25,
By reversing the current direction by the transistor 26, the transistor 20, the resistor 24, the resistor 27, and the resistor 21 and blowing out from the emitter terminal of the transistor 4, it becomes possible to compensate the current flowing from the reference resistor string. By performing this current compensation, the differential input voltage V IH −V IL can be accurately applied across the reference resistor string.

【0015】以上のように、この実施例によれば、基準
抵抗列を流れる電流を補償することにより、差動入力電
圧VIH−VILを正確に基準抵抗列の両端に印加すること
ができる。なお、この実施例では、基準抵抗列を流れる
電流の補償を行う回路にPNPトランジスタとNPNト
ランジスタと抵抗を用いたが、PチャンネルMOSトラ
ンジスタとNチャンネルMOSトランジスタを用いても
同様の効果が得られるのは明白である。
As described above, according to this embodiment, the differential input voltage V IH -V IL can be accurately applied to both ends of the reference resistance series by compensating the current flowing through the reference resistance series. . In this embodiment, the PNP transistor, the NPN transistor and the resistor are used in the circuit for compensating the current flowing through the reference resistor string, but the same effect can be obtained by using the P channel MOS transistor and the N channel MOS transistor. Is obvious.

【0016】[0016]

【発明の効果】この発明の基準電圧発生回路は、差動入
力信号を受けるエミッタホロワの入出力間の非線形特性
の影響を受けることなく、基準電圧を分圧する抵抗列の
両端に差動入力電圧VIH−VILを正確に印加することが
できるという格別の効果を奏する。
According to the reference voltage generating circuit of the present invention, the differential input voltage V is applied across the resistor string for dividing the reference voltage without being affected by the non-linear characteristic between the input and output of the emitter follower receiving the differential input signal. It has a special effect that IH- V IL can be accurately applied.

【図面の簡単な説明】[Brief description of drawings]

【図1】この発明の一実施例における基準電圧発生回路
の回路図である。
FIG. 1 is a circuit diagram of a reference voltage generating circuit according to an embodiment of the present invention.

【図2】従来の基準電圧発生回路の回路図である。FIG. 2 is a circuit diagram of a conventional reference voltage generating circuit.

【符号の説明】[Explanation of symbols]

1 第1の定電位 2,4 エミッタホロワ用のトランジスタ 3a〜3b 抵抗値Rの基準抵抗 5,6 電流値I0 の定電流源 7 第2の定電位 8 第2の入力端子 9 第1の入力端子 10,14,18,21,22,24,27 抵抗 11,15,19,23,25 PNPトランジスタ 12,16 電流検出用のトランジスタ 13,17 抵抗値4Rの抵抗 20,26 NPNトランジスタ 28 エミッタホロワ回路 29 電流検出回路 30 電流補償回路1 1st constant potential 2, 4 Transistor for emitter follower 3a-3b Reference resistance of resistance value 5, 6 Constant current source of current value I 0 7 2nd constant potential 8 2nd input terminal 9 1st input Terminals 10, 14, 18, 21, 22, 24, 27 Resistors 11, 15, 19, 23, 25 PNP transistors 12, 16 Current detecting transistors 13, 17 Resistors with resistance value 4R 20, 26 NPN transistors 28 Emitter follower circuits 29 Current detection circuit 30 Current compensation circuit

Claims (2)

【特許請求の範囲】[Claims] 【請求項1】 第1の入力端子がベースに接続されたエ
ミッタホロワ用の第1のトランジスタと、第2の入力端
子がベースに接続されたエミッタホロワ用の第2のトラ
ンジスタと、前記第1,第2のトランジスタのエミッタ
間に直列接続された複数の抵抗とからなるエミッタホロ
ワ回路と、 前記第1,第2のトランジスタの各エミッタに入力端が
接続され、前記エミッタの各電位に応じた検出電流を発
生するとともに電流値の大きい第1の検出電流から電流
値の小さい第2の検出電流を差し引いた検出出力電流を
発生する電流検出回路と、 前記検出出力電流を入力とし、前記検出出力電流を正極
性と負極性の補償電流に変換して、前記正極性の補償電
流を前記第1のトランジスタのエミッタに供給し、かつ
前記負極性の補償電流を前記第2のトランジスタのエミ
ッタに供給する電流補償回路とを備えた基準電圧発生回
路。
1. A first transistor for an emitter follower having a first input terminal connected to a base, a second transistor for an emitter follower having a second input terminal connected to a base, and the first and the first transistors. An emitter follower circuit including a plurality of resistors connected in series between the emitters of the two transistors, and an input terminal connected to each emitter of the first and second transistors, and a detection current corresponding to each potential of the emitter. A current detection circuit that generates a detection output current that is generated and that has a second detection current with a small current value subtracted from a first detection current with a large current value; and the detection output current as an input, and the detection output current is a positive electrode. And a negative compensation current is supplied to the emitter of the first transistor, and the negative compensation current is converted to the second compensation current. Reference voltage generating circuit that includes a current compensation circuit for supplying to the emitter of the transistor.
【請求項2】 電流検出回路は、第1のトランジスタの
エミッタがベースに接続された第3のトランジスタのエ
ミッタに第1の抵抗の一端が接続され、第2のトランジ
スタのエミッタがベースに接続された第4のトランジス
タのエミッタに第2の抵抗の一端が接続され、前記第
1,第2の抵抗の他端が共通接続され、かつ、前記第4
のトランジスタのコレクタ電流をミラー反転した電流と
前記第3のトランジスタのコレクタ電流を加算して検出
出力電流としてを出力する構成であることを特徴とする
請求項1記載の基準電圧発生回路。
2. The current detecting circuit, wherein the emitter of the first transistor is connected to the base, the emitter of the third transistor is connected to one end of the first resistor, and the emitter of the second transistor is connected to the base. One end of the second resistor is connected to the emitter of the fourth transistor, the other ends of the first and second resistors are commonly connected, and the fourth resistor is connected.
2. The reference voltage generating circuit according to claim 1, wherein the collector current of the transistor is mirror-inverted and the collector current of the third transistor is added to output as a detection output current.
JP13042993A 1993-06-01 1993-06-01 Reference voltage generating circuit Pending JPH06343044A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP13042993A JPH06343044A (en) 1993-06-01 1993-06-01 Reference voltage generating circuit

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP13042993A JPH06343044A (en) 1993-06-01 1993-06-01 Reference voltage generating circuit

Publications (1)

Publication Number Publication Date
JPH06343044A true JPH06343044A (en) 1994-12-13

Family

ID=15034033

Family Applications (1)

Application Number Title Priority Date Filing Date
JP13042993A Pending JPH06343044A (en) 1993-06-01 1993-06-01 Reference voltage generating circuit

Country Status (1)

Country Link
JP (1) JPH06343044A (en)

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0715238A3 (en) * 1994-12-01 1997-07-30 Texas Instruments Inc Circuit and method for regulating a voltage
US6724234B1 (en) * 1999-09-17 2004-04-20 Nortel Networks Limited Signal-level compensation for communications circuits

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0715238A3 (en) * 1994-12-01 1997-07-30 Texas Instruments Inc Circuit and method for regulating a voltage
US6724234B1 (en) * 1999-09-17 2004-04-20 Nortel Networks Limited Signal-level compensation for communications circuits

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