JPH05316735A - Sine wave pwm controlling method for inverter - Google Patents

Sine wave pwm controlling method for inverter

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Publication number
JPH05316735A
JPH05316735A JP4115039A JP11503992A JPH05316735A JP H05316735 A JPH05316735 A JP H05316735A JP 4115039 A JP4115039 A JP 4115039A JP 11503992 A JP11503992 A JP 11503992A JP H05316735 A JPH05316735 A JP H05316735A
Authority
JP
Japan
Prior art keywords
inverter
control
conduction
time
sine wave
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
JP4115039A
Other languages
Japanese (ja)
Inventor
Tatsuya Suzuki
達也 鈴木
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Fuji Electric Co Ltd
Original Assignee
Fuji Electric Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Fuji Electric Co Ltd filed Critical Fuji Electric Co Ltd
Priority to JP4115039A priority Critical patent/JPH05316735A/en
Publication of JPH05316735A publication Critical patent/JPH05316735A/en
Pending legal-status Critical Current

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  • Control Of Ac Motors In General (AREA)
  • Inverter Devices (AREA)

Abstract

PURPOSE:To optimally operate an inverter to be PWM-controlled with an induction motor as a load to increase an output voltage and to decrease a waveform distortion in an overmodulation state. CONSTITUTION:A time tn in which instantaneous values of a carrier Vc and a sine wave control signal Vs become equal is calculated, whether the time tn is larger than time ((Tc/2)-td) or not is decided, and a larger case is Y, not larger case is N. If an output frequency fi of an inverter is its predetermined value fic or less and a result of decision of the time is N, a time to of I/2 value of a predetermined PWM control pulse width is (tn-td), while if it is Y, the time to is ((Tc/2)-td), and both are controlled to be partly conducted. On the other hand, if the frequency fi is larger than the value fic and a result of the decision of the time is N, the time to is (tn-td) to be controlled to be partly conducted. On the contrary, at the time of Y, the time to is (Tc/2) to be controlled to be entirely conducted.

Description

【発明の詳細な説明】Detailed Description of the Invention

【0001】[0001]

【産業上の利用分野】本発明は誘導電動機を可変速駆動
するインバータの正弦波PWM制御方法に関する。
BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a sine wave PWM control method for an inverter that drives an induction motor at a variable speed.

【0002】[0002]

【従来の技術】先ずインバータの正弦波PWM制御を、
その制御動作が図3に示す制御動作図の如く行われる場
合を例として説明する。今、その振幅Es がインバータ
出力電圧の比例値とされ且つその周波数がインバータ出
力周波数と等しくなされた正弦波制御信号をVs とし、
またその波高値2Ec とその周期Tc とがそれぞれ一定
とされ且つその大きさが+Ec と−Ec間にて繰り返し
変化する鋸歯状搬送波をVc とし、該搬送波Vc の各周
期毎に該搬送波と前記制御信号Vs との大きさの瞬時値
比較を行い、該搬送波の第n番目の周期において前記両
瞬時値が等しくなる時点の該周期開始時点からの経過時
間をtn とし、更に前記インバータの主回路変換部ブリ
ッジ構成の上下両アームにおける各スイッチング素子間
の同時導通防止用デッドタイムをtd とした場合、該各
アーム素子に対するPWM制御された基本導通指令信号
のパルス幅の1/2値をなす時間to は下記の式(1)
により、また前記時間tn とその構成要因をなす変調比
λとはそれぞれ下記の式(2)と式(3)とにより決定
される。なお式(2)中のθn は前記搬送波Vc におけ
る第n番目の周期における前記の制御信号Vs の平均位
相角である。
2. Description of the Related Art First, sine wave PWM control of an inverter
A case where the control operation is performed as shown in the control operation diagram of FIG. 3 will be described as an example. Now, let V s be a sine wave control signal whose amplitude E s is a proportional value of the inverter output voltage and whose frequency is equal to the inverter output frequency.
Also a sawtooth carrier wave and the wave height value 2E c and its period T c is, each is a constant and the magnitude of changing repeatedly at between + E c and -E c and V c, for each period of the carrier wave V c Then, the instantaneous value of the magnitude of the carrier and the control signal V s is compared, and the elapsed time from the start of the cycle at the time when the instantaneous values of the carrier become equal in the n-th cycle is defined as t n. Further, when the dead time for preventing simultaneous conduction between the switching elements in the upper and lower arms of the main circuit conversion section bridge structure of the inverter is t d , the pulse width of the PWM-controlled basic conduction command signal for the respective arm elements is The time t o that forms a half value of is expressed by the following equation (1).
Further, the time t n and the modulation ratio λ that constitutes the constituent factor are determined by the following equations (2) and (3), respectively. Note that θ n in the equation (2) is the average phase angle of the control signal V s in the n-th cycle of the carrier wave V c .

【0003】 to =tn −td ‥‥‥‥‥‥‥‥‥‥‥(1) tn =(Tc /4) ( λ sinθn +1)‥‥‥(2) λ=Es /Ec ‥‥‥‥‥‥‥‥‥‥‥‥(3) 従って前記の基本導通指令信号は、前記搬送波Vc のn
=1,2,‥‥の如く連続する各周期毎にその1/2時
点を中心とし各々その幅を2to として得られたパルス
からなるパルス列を形成するものとなり、また前記の各
アーム素子それぞれに対する導通指令信号は前記基本導
通指令信号に対しそれぞれ所定の位相差を有して決定さ
れたものとなる。
T o = t n −t d ‥‥‥‥‥‥‥‥‥‥‥‥‥‥‥ (1) t n = (T c / 4) (λ sin θ n +1) ‥‥‥‥ (2) λ = E s / E c ‥‥‥‥‥‥‥‥‥‥‥‥‥‥‥‥‥ (3) Therefore, the basic conduction command signal is n of the carrier wave V c .
= 1,2, becomes as forming a pulse train consisting of each its width around its 1/2 point for each successive periods as ‥‥ obtained as 2t o pulses and each respective arm elements of the The conduction command signal for the signal is determined to have a predetermined phase difference with respect to the basic conduction command signal.

【0004】更に誘導電動機をその負荷とするインバー
タでは、該電動機に対する磁束一定制御を行うために、
該インバータの出力に関しその電圧対周波数比を一定と
なす制御が一般に行われており、従って前記変調比λも
またインバータ出力周波数の増大と共に所定の勾配にて
増大するものとなされている。ここで、従来のこの種の
正弦波PWM制御方法としては、前記の如き変調比λが
1より大となる過変調状態において上記の式(2)によ
り規定される時間tnが(Tc /2)−td より大とな
った場合に、前記ブリッジ構成のアーム各素子を全て通
流率1の全導通状態となすもの、或いはTc −2td
導通期間としその通流率を1−2td /Tc となす部分
導通制御を行うものが知られている。
Further, in an inverter using an induction motor as its load, in order to carry out constant flux control for the electric motor,
The output of the inverter is generally controlled so that its voltage-to-frequency ratio is constant, so that the modulation ratio λ also increases with a predetermined slope as the inverter output frequency increases. Here, as a conventional sine wave PWM control method of this type, the time t n defined by the above equation (2) is (T c / in the overmodulation state in which the modulation ratio λ is greater than 1 as described above. 2) When it becomes larger than -t d , all the arm elements of the bridge structure are in a full conduction state with a conduction rate of 1, or T c -2t d is a conduction period and the conduction rate is 1 It is known to perform partial conduction control of −2t d / T c .

【0005】なお図4は前記の如きPWM制御時におけ
る諸信号の動作波形図の例示であり図4(イ)は過変調
状態にある前記の制御信号Vs と搬送波Vc との相対関
係を示し、また図4(ロ)と図4(ハ)とはそれぞれ前
記の部分導通制御時と全導通制御時とに対応する基本導
通指令信号Sswp とSswf とを示す。また図5はインバ
ータ出力電圧の対変調比特性図であり、図示の如く変調
比λが大なる領域におけるインバータ出力電圧Vi は特
性線Lf で示した前記全導通制御時の方が特性線Lp
示した前記部分導通制御時のものより大となる。
FIG. 4 is an example of an operation waveform diagram of various signals during the PWM control as described above, and FIG. 4A shows the relative relationship between the control signal V s and the carrier wave V c in the overmodulation state. 4B and 4C show basic conduction command signals S swp and S swf corresponding to the partial conduction control and the full conduction control, respectively. Further, FIG. 5 is a characteristic diagram of the inverter output voltage versus modulation ratio. As shown in the figure, the inverter output voltage V i in the region where the modulation ratio λ is large is the characteristic line shown by the characteristic line L f during the full conduction control. It is larger than that in the partial conduction control shown by L p .

【0006】[0006]

【発明が解決しようとする課題】しかしながら前記の如
き従来の正弦波PWM制御方法によれば、前記の正弦波
制御信号Vs の1周期中において前記時間tn が(Tc
/2)−td 以上となる区間に対してその通流率を1と
なす全導通制御を行う場合、該区間において前記搬送波
c の1周期当たりの前記インバータ出力電圧Vi の変
動量が他の区間におけるそれよりも大となるため該出力
電圧Vi の正弦波波形からの波形歪も大となり、これに
伴い前記インバータの負荷となる誘導電動機の効率の低
下或いはその振動と騒音の増大等を招いていた。
However, according to the conventional sine wave PWM control method as described above, the time t n is (T c in one cycle of the sine wave control signal V s.
/ 2) -t d or more, when performing full conduction control in which the conduction ratio is 1 in the section, the fluctuation amount of the inverter output voltage V i per cycle of the carrier wave V c in the section is Since it is larger than that in other sections, the waveform distortion of the sine wave waveform of the output voltage V i also becomes large, and along with this, the efficiency of the induction motor serving as the load of the inverter is lowered or its vibration and noise are increased. And so on.

【0007】また上記と同様の条件下でその通流率を1
−2td /Tc となす部分導通制御を行う場合、前記の
如きインバータ出力電圧の波形歪は相対的に小となり該
波形歪に伴う諸問題は軽減されるが、その運転特性上前
記誘導電動機に対する大なる供給電圧を要する場合に供
給電圧不足を来すことがあった。上記に鑑み本発明は、
前記の全導通制御と部分導通制御とを前記インバータの
出力周波数に従って切換え併用し該両制御の利点を生か
す正弦波PWM制御方法の提供を目的とするものであ
る。
Under the same conditions as above, the flow rate is 1
When performing partial conduction control formed between -2t d / T c, the waveform distortion of the such inverter output voltage is relatively small and the problems associated with the waveform distortion becomes is reduced, the driving characteristics on the induction motor There was a case where the supply voltage became insufficient when a large supply voltage was required. In view of the above, the present invention is
It is an object of the present invention to provide a sine wave PWM control method in which the full conduction control and the partial conduction control are switched and used in accordance with the output frequency of the inverter and the advantages of the both controls are utilized.

【0008】[0008]

【課題を解決するための手段】上記目的を達成するため
に、本発明のインバータの正弦波PWM制御方法は、そ
の周波数がインバータ出力周波数と等しく且つその振幅
がインバータ出力電圧に比例した正弦波制御信号と波高
値一定の鋸歯状搬送波との大きさの瞬時値比較を行い、
該比較結果に従って前記搬送波の1周期毎にインバータ
主回路スイッチング素子の断続動作における通流率を指
定する正弦波PWM制御方法において、前記搬送波の波
高値の1/2値に対する前記制御信号の振幅の比とされ
た変調比が1より大となる過変調時には、前記通流率を
1となす全導通制御と前記搬送波の周期より所定のデッ
ドタイムを減じた期間を導通期間として前記通流率を1
より小となす部分導通制御とを切換え併用するものと
し、また該制御状態の切換えをインバータ出力周波数の
所定値において行うものとなし該周波数所定値より大な
る領域においては前記の全導通制御を行いまた該周波数
所定値以下の領域においては前記の部分導通制御を行う
ものとし、更に該制御状態の切換え時に同時に前記変調
比をその新たな所定値に切換えるものとし、且つ該変調
比の新たな所定値を前記制御状態の切換えに伴うインバ
ータ出力電圧の変動を零となす如くインバータ出力周波
数に対応した値として予め決定するものとする。
To achieve the above object, a sine wave PWM control method for an inverter according to the present invention is a sine wave control whose frequency is equal to an inverter output frequency and whose amplitude is proportional to an inverter output voltage. Performs an instantaneous value comparison of the signal and the sawtooth carrier wave with a constant peak value,
In a sinusoidal PWM control method for designating a duty factor in an intermittent operation of an inverter main circuit switching element for each cycle of the carrier wave according to the comparison result, in the amplitude of the control signal with respect to a half value of the peak value of the carrier wave. In the case of overmodulation in which the defined modulation ratio is greater than 1, the conduction ratio is set to a conduction period in which the conduction period is set to 1 and a period in which a predetermined dead time is subtracted from the carrier wave period is used as the conduction period. 1
A smaller partial conduction control is used together with switching, and the switching of the control state is performed at a predetermined value of the inverter output frequency, and none is performed at the frequency higher than the predetermined value. Further, the partial conduction control is performed in a region below the frequency predetermined value, the modulation ratio is switched to the new predetermined value at the same time when the control state is switched, and the new predetermined modulation ratio is set. The value is predetermined as a value corresponding to the inverter output frequency so that the variation of the inverter output voltage due to the switching of the control state is zero.

【0009】[0009]

【作用】前記の如く、正弦波PWM制御されるインバー
タの出力電圧はPWM演算においてその搬送波と瞬時値
比較される正弦波制御信号の振幅に応じて変更制御さ
れ、従って該制御信号と振幅一定の前記搬送波との振幅
比として与えられる変調比によってもまた変化する。更
に誘導電動機をその負荷とするインバータにおいてはそ
の出力電圧と出力周波数との比が通常の制御範囲におい
て一定値に制御されており、従って前記変調比はインバ
ータ出力周波数の増大と共に増大するものとなる。即
ち、誘導電動機をその負荷とするインバータにおいてそ
の出力電圧はその出力周波数と前記変調比とに関連して
制御されるものとなる。
As described above, the output voltage of the sine wave PWM controlled inverter is controlled to be changed according to the amplitude of the sine wave control signal whose instantaneous value is compared with that of the carrier wave in the PWM calculation. It also varies with the modulation ratio given as the amplitude ratio with the carrier. Further, in the inverter using the induction motor as its load, the ratio of the output voltage to the output frequency is controlled to be a constant value in the normal control range, so that the modulation ratio increases with the increase of the inverter output frequency. .. That is, the output voltage of the inverter whose load is the induction motor is controlled in relation to the output frequency and the modulation ratio.

【0010】従って、インバータ出力周波数の増大に伴
い前記変調比も増大して過変調状態に至った場合におけ
る前記の全導通制御と部分導通制御との制御状態の切換
えを前記インバータの所定の出力周波数において行うと
共に、同時に前記変調比をその新たな変調比に変更し、
且つ該新たな変調比を前記の制御状態の切換えに伴うイ
ンバータ出力電圧の変動を零となす如く前記インバータ
出力周波数に対応した値として予め決定しておくことに
より、前記インバータ出力電圧の変動を伴わずに前記両
制御状態間の相互切換えが可能となる。
Therefore, when the modulation ratio increases with the increase of the inverter output frequency and the overmodulation state is reached, the control state is switched between the full conduction control and the partial conduction control at the predetermined output frequency of the inverter. And at the same time change the modulation ratio to the new modulation ratio,
Further, by predetermining the new modulation ratio as a value corresponding to the inverter output frequency so that the variation of the inverter output voltage due to the switching of the control state becomes zero, the variation of the inverter output voltage is caused. It becomes possible to switch between the two control states without the need of the above.

【0011】上記に従い本発明は、誘導電動機を可変速
制御するインバータの正弦波PWM制御において、前記
の如き変調比の同時切換えを伴いながら前記の全導通制
御と部分導通制御とのインバータ出力周波数に対応した
切換えを行うことにより、該切換えに伴うインバータ出
力電圧の変動を回避させながら前記両導通制御の併用を
可能となすものである。
In accordance with the above, the present invention provides the inverter output frequency for the full conduction control and the partial conduction control in the sine wave PWM control of the inverter for variable speed control of the induction motor while simultaneously switching the modulation ratio as described above. By performing the corresponding switching, it is possible to use the both conduction controls together while avoiding the fluctuation of the inverter output voltage due to the switching.

【0012】[0012]

【実施例】以下本発明の実施例を図1に示す制御フロー
チャートと、図2に示す変調比の対インバータ出力周波
数特性図とに従って説明する。先ず図1の制御フローチ
ャートにより前記正弦波PWM制御を説明する。なお本
フローチャートに示す諸量は各々前記図3の制御動作図
中に示すものと同一のものである。
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS An embodiment of the present invention will be described below with reference to a control flow chart shown in FIG. 1 and an inverter output frequency characteristic diagram of modulation ratio shown in FIG. First, the sine wave PWM control will be described with reference to the control flowchart of FIG. The quantities shown in this flowchart are the same as those shown in the control operation diagram of FIG.

【0013】先ず、前記搬送波Vc の連続する各周期の
第n番目の周期において(但しn=1,2,‥‥)前記
時間tn を前記式(2)に従って演算し、また前記の如
き全導通制御と部分導通制御との制御状態の切換えを行
うインバータ出力周波数fiの所定値をficとしこれを
例えば80HZ の如く決定する。次に、前記時間tn
時間〔(Tc /2)−td 〕より大であるか否かの判定
を行い、大なる状態をY,以下である状態をNとなす時
間判定を行う。
First, in the nth cycle of each successive cycle of the carrier wave V c (where n = 1, 2, ...), the time t n is calculated in accordance with the equation (2), and as described above. A predetermined value of the inverter output frequency f i for switching between the control states of the full conduction control and the partial conduction control is f ic , which is determined as 80H Z , for example. Next, it is determined whether or not the time t n is longer than the time [(T c / 2) -t d ], and the time is determined such that the greater state is Y and the lesser state is N. ..

【0014】上記の各準備の後に、以下の如き4通りの
選択を行う。即ちその第1の選択は、前記インバータ出
力周波数fi が例えば80HZ となされたその切換え用
所定値fic以下であり且つ前記時間判定の結果がNの状
態であれば、前記のPWM制御された基本導通指令信号
のパルス幅の1/2値をなす時間to を前記式(1)に
従い前記のデッドタイムtd を用いてtn −td となす
ものである。
After each of the above preparations, the following four selections are made. That first selection thereof, the inverter output frequency f i or less, for example, 80H Z and made the the changeover predetermined value f ics and the time determination result if the condition of N, the said PWM control The time t o that forms a half value of the pulse width of the basic conduction command signal is set to t n -t d by using the dead time t d according to the equation (1).

【0015】次にその第2の選択は、前記周波数fi
前記所定値fic以下であり且つ前記時間判定の結果がY
の状態であれば、前記時間to を(Tc /2)−td
なすものである。またその第3の選択は、前記周波数f
i が前記所定値ficより大であって且つ前記前記時間判
定の結果がNの状態であれば、前記時間to を前記tn
−td となすものである。
Next, in the second selection, the frequency f i is equal to or less than the predetermined value f ic and the result of the time determination is Y.
In this state, the time t o is (T c / 2) -t d . The third choice is the frequency f
If i is larger than the predetermined value f ic and the result of the time determination is N, the time t o is set to t n.
-T d .

【0016】更にその第4の選択は、前記周波数fi
前記所定値ficより大であって且つ前記前記時間判定の
結果がYの状態であれば、前記時間to をTc /2とな
すものである。即ち前記PWM制御は、前記第4の選択
においてはその通流率が1となされる全導通制御とな
り、また前記第1〜第3の選択においてはその通流率が
1より小となされる部分導通制御となる。
Further, in the fourth selection, when the frequency f i is larger than the predetermined value f ic and the result of the time determination is Y, the time t o is T c / 2. It is something to say. That is, the PWM control is a full conduction control in which the conduction ratio is 1 in the fourth selection, and a portion in which the conduction ratio is less than 1 in the first to third selections. It becomes conduction control.

【0017】次に図2に示す変調比λの対インバータ出
力周波数fi 特性図は、インバータ運転における該出力
周波数fi の変動に対応する変調比λの追従制御模様を
示すものであり、前記周波数所定値fic(例えば80H
Z )においては前記の全導通制御と部分導通制御との制
御状態切換えと共に、該制御状態切換えに伴うインバー
タ出力電圧の変動を零となす如く、前記変調比λのλ1
とλ2 間の不連続切換えが行われる模様を示すものであ
る。
[0017] Next versus inverter output frequency f i characteristic diagram of the modulation ratio λ shown in FIG. 2 shows a following control patterns of the modulation ratio λ corresponding to the variation of the output frequency f i in the inverter operation, wherein Frequency predetermined value f ic (eg 80H
In Z ), the control state is switched between the full conduction control and the partial conduction control, and the modulation ratio λ of λ 1 is set so that the variation of the inverter output voltage due to the control state switching becomes zero.
It shows that discontinuous switching between λ 2 and λ 2 is performed.

【0018】なお、図2に示す如きインバータ出力周波
数fi に対する変調比λの値は予めλ(変調比)テーブ
ルとして決定されるものであり、インバータの正弦波P
WM制御回路においてソフトウェアとして準備されてい
るものである。なおまた、前記λテーブルの作成におい
て前記周波数fi の変化はその分解能による制約を受け
て連続的なものとはならない。従って図2に示す特性は
実際は前記周波数分解能を最小変化単位とする階段状の
変化をなすものとなる。ここに前記分解能は例えば0.
25HZ の如く選定される。
The value of the modulation ratio λ with respect to the inverter output frequency f i as shown in FIG. 2 is determined in advance as a λ (modulation ratio) table, and the sine wave P of the inverter is used.
It is prepared as software in the WM control circuit. Further, in the creation of the λ table, the change of the frequency f i is not continuous because it is restricted by the resolution. Therefore, the characteristic shown in FIG. 2 actually exhibits a stepwise change with the frequency resolution as the minimum change unit. Here, the resolution is, for example,
25H Z as is selected.

【0019】[0019]

【発明の効果】本発明によれば、その周波数がインバー
タ出力周波数と等しく且つその振幅がインバータ出力電
圧に比例した正弦波制御信号と波高値一定の鋸歯状搬送
波との大きさの瞬時値比較を行い、該比較結果に従って
前記搬送波の1周期毎にインバータ主回路スイッチング
素子の断続動作における通流率を指定する正弦波PWM
制御方法において、前記の搬送波と制御信号間の振幅比
とされる変調比が1より大となる過変調時には、前記イ
ンバータ出力周波数の所定設定値を境に該周波数設定値
より大なる領域においては前記通流率を1となす全導通
制御を行い、また前記周波数設定値以下の領域において
は前記通流率を1より所定値だけ小となす部分導通制御
を行う如く前記両制御状態の切換え併用を行うことによ
り、前記の過変調状態における周波数領域におけるイン
バータ負荷誘導電動機の出力トルクピーク値を例えばそ
の定格値の約10%等可成り増大させることが可能とな
り、且つまた前記両制御状態の切換え時に前記変調比を
予め決定されているその新たな値へ同時に切換えること
により該制御状態の切換えに伴うインバータ出力電圧の
変動を零となした円滑な運転を図ることができる。
According to the present invention, an instantaneous value comparison of the magnitude of a sine wave control signal whose frequency is equal to the inverter output frequency and whose amplitude is proportional to the inverter output voltage and a sawtooth carrier having a constant peak value is performed. A sine-wave PWM that specifies the conduction ratio in the intermittent operation of the inverter main circuit switching element for each cycle of the carrier wave according to the comparison result.
In the control method, at the time of overmodulation in which the modulation ratio, which is the amplitude ratio between the carrier wave and the control signal, is greater than 1, in a region where the inverter output frequency is greater than the frequency setting value with a predetermined setting value as a boundary, Switching between both control states is performed such that full conduction control with the conduction ratio of 1 is performed, and partial conduction control with the conduction ratio less than 1 by a predetermined value is performed in the region below the frequency setting value. By doing so, it becomes possible to considerably increase the output torque peak value of the inverter load induction motor in the frequency region in the overmodulation state, for example, about 10% of its rated value, and also switch between the two control states. At the same time, the variation of the inverter output voltage due to the switching of the control state is made zero by simultaneously switching the modulation ratio to the predetermined new value. It is possible to smooth a driving.

【図面の簡単な説明】[Brief description of drawings]

【図1】本発明の実施例を示す制御フローチャートFIG. 1 is a control flowchart showing an embodiment of the present invention.

【図2】本発明の実施例を示す変調比の対インバータ出
力周波数特性図
FIG. 2 is a characteristic diagram of modulation ratio vs. inverter output frequency characteristic showing an embodiment of the present invention.

【図3】インバータの正弦波PWM制御の制御動作図FIG. 3 is a control operation diagram of sine wave PWM control of an inverter.

【図4】インバータの正弦波PWM制御時の制御信号動
作波形図
FIG. 4 is a control signal operation waveform diagram during sine-wave PWM control of the inverter.

【図5】インバータ出力電圧の対変調比特性図FIG. 5: Inverter output voltage vs. modulation ratio characteristic diagram

【符号の説明】[Explanation of symbols]

i インバータ出力周波数 fic 導通制御状態切換え用のインバータ出力周波数の
設定値 Tc 搬送波周期 td 各スイッチング素子間の同時導通防止用デッドタ
イム tn PWM制御された原導通指令信号のパルス幅の1
/2値 to PWM制御された導通指令信号のパルス幅の1/
2値 Vi インバータ出力電圧 λ 変調比 θn 搬送波の第n番目周期における正弦波制御信号の
平均位相角
f i Inverter output frequency f ic Setting value of inverter output frequency for conduction control state switching T c Carrier wave period t d Dead time for preventing simultaneous conduction between switching elements t n PWM pulse width of original conduction command signal 1
/ 2 value t o 1 / of the pulse width of the PWM-controlled conduction command signal
Binary V i Inverter output voltage λ Modulation ratio θ n Average phase angle of sine wave control signal in nth cycle of carrier wave

Claims (4)

【特許請求の範囲】[Claims] 【請求項1】その周波数がインバータの出力周波数と等
しく且つその振幅が該インバータの出力電圧に比例した
正弦波制御信号と波高値一定の鋸歯状搬送波との大きさ
の瞬時値比較を行い、該比較結果に従い前記搬送波の1
周期毎に前記インバータの主回路スイッチング素子の断
続動作における通流率を指定するインバータの正弦波P
WM制御方法において、前記搬送波の波高値の1/2値
に対する前記制御信号の振幅の比とされた変調比が1よ
り大となる過変調時には、前記通流率を1となす全導通
制御と前記搬送波の周期より所定のデッドタイムを減じ
た期間を導通期間として前記通流率を1より小となす部
分導通制御とを切換え併用することを特徴とするインバ
ータの正弦波PWM制御方法。
1. A sine-wave control signal whose frequency is equal to the output frequency of an inverter and whose amplitude is proportional to the output voltage of the inverter and an instantaneous value comparison of the magnitude of a sawtooth carrier having a constant peak value, 1 of the carrier wave according to the comparison result
The sine wave P of the inverter that specifies the conduction ratio in the intermittent operation of the main circuit switching element of the inverter for each cycle
In the WM control method, in the case of overmodulation in which the modulation ratio, which is the ratio of the amplitude of the control signal to the half value of the peak value of the carrier wave, is greater than 1, the full conduction control in which the conduction ratio is 1 is performed. A sine wave PWM control method for an inverter, characterized in that a period obtained by subtracting a predetermined dead time from the cycle of the carrier wave is set as a conduction period and partial conduction control for making the conduction ratio smaller than 1 is switched and used in combination.
【請求項2】請求項1記載のインバータの正弦波PWM
制御方法において、前記の全導通制御と部分導通制御と
の制御状態の切換えをインバータ出力周波数の所定値に
おいて行うものとなし、該出力周波数の所定値より大な
る領域においては前記の全導通制御を行いまた該所定値
以下の領域においては前記の部分導通制御を行うことを
特徴とするインバータの正弦波PWM制御方法。
2. The sine wave PWM of the inverter according to claim 1.
In the control method, the switching of the control states of the full conduction control and the partial conduction control is not performed at a predetermined value of the inverter output frequency, and the full conduction control is performed in a region larger than the predetermined value of the output frequency. A sine wave PWM control method for an inverter, characterized in that the partial conduction control is performed in a region below the predetermined value.
【請求項3】請求項2記載のインバータの正弦波PWM
制御方法において、前記の如き制御状態の切換え時に、
同時に前記変調比をその新たな所定値に切換えることを
特徴とするインバータの正弦波PWM制御方法。
3. The sine wave PWM of the inverter according to claim 2.
In the control method, when switching the control state as described above,
At the same time, the modulation ratio is switched to the new predetermined value, and a sine wave PWM control method for an inverter.
【請求項4】請求項3記載のインバータの正弦波PWM
制御方法において、前記変調比の新たな所定値を、前記
制御状態の切換えに伴うインバータ出力電圧の変動を零
となす如くインバータ出力周波数に対応した値として予
め決定することを特徴とするインバータの正弦波PWM
制御方法。
4. A sine wave PWM of the inverter according to claim 3.
In the control method, the new predetermined value of the modulation ratio is determined in advance as a value corresponding to the inverter output frequency so that the variation of the inverter output voltage due to the switching of the control state becomes zero. Wave PWM
Control method.
JP4115039A 1992-05-08 1992-05-08 Sine wave pwm controlling method for inverter Pending JPH05316735A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP4115039A JPH05316735A (en) 1992-05-08 1992-05-08 Sine wave pwm controlling method for inverter

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP4115039A JPH05316735A (en) 1992-05-08 1992-05-08 Sine wave pwm controlling method for inverter

Publications (1)

Publication Number Publication Date
JPH05316735A true JPH05316735A (en) 1993-11-26

Family

ID=14652686

Family Applications (1)

Application Number Title Priority Date Filing Date
JP4115039A Pending JPH05316735A (en) 1992-05-08 1992-05-08 Sine wave pwm controlling method for inverter

Country Status (1)

Country Link
JP (1) JPH05316735A (en)

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CN110405250A (en) * 2018-04-28 2019-11-05 南京德朔实业有限公司 circular saw

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2010104151A (en) * 2008-10-23 2010-05-06 Toyota Motor Corp Control device and control method for ac motor
JP4506889B2 (en) * 2008-10-23 2010-07-21 トヨタ自動車株式会社 AC motor control apparatus and control method
US8502493B2 (en) 2008-10-23 2013-08-06 Toyota Jidosha Kabushiki Kaisha Control device and control method for alternating-current motor
US10148166B2 (en) 2014-08-28 2018-12-04 Mitsubishi Electric Corporation Power converter and vehicle driving system
JP2016052250A (en) * 2015-11-19 2016-04-11 三菱電機株式会社 Power conversion device and vehicle drive system
CN110405250A (en) * 2018-04-28 2019-11-05 南京德朔实业有限公司 circular saw

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