JPH0284069A - Dc power device - Google Patents

Dc power device

Info

Publication number
JPH0284069A
JPH0284069A JP23397088A JP23397088A JPH0284069A JP H0284069 A JPH0284069 A JP H0284069A JP 23397088 A JP23397088 A JP 23397088A JP 23397088 A JP23397088 A JP 23397088A JP H0284069 A JPH0284069 A JP H0284069A
Authority
JP
Japan
Prior art keywords
current
voltage
value
choke coil
switching element
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
JP23397088A
Other languages
Japanese (ja)
Inventor
Shigeru Sone
曽根 茂
Masaoki Sekine
正興 関根
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Origin Electric Co Ltd
Original Assignee
Origin Electric Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Origin Electric Co Ltd filed Critical Origin Electric Co Ltd
Priority to JP23397088A priority Critical patent/JPH0284069A/en
Publication of JPH0284069A publication Critical patent/JPH0284069A/en
Pending legal-status Critical Current

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  • Dc-Dc Converters (AREA)

Abstract

PURPOSE:To prevent increase of switching loss and generation of noise by driving a switching element of a main circuit with a voltage comparator having a hysteresis characteristic of a proportional value and a multiplication signal of the absolute value of the current through a choke coil in the main circuit. CONSTITUTION:As compared with a reference sinusoidal wave voltage Vr by a comparator 8, a switching element 4 is driven when the current proportional value vii gets to the reference sinusoidal wave voltage Vr, if t=t1. If t=t2, and when the current proportional value vii gets to the reference sinusoidal wave voltage Vr, the drive of the switching element 4 is interrupted. In the area where the switching element 4 is ON, energy is accumulated to a choke coil 3. With the element 4 OFF, the energy accumulated to the choke coil 3 is released to a load RL through a flywheel diode 5. By switching this element 4, the input current waveform is to be a continuation of high frequency triangular waveform. The envelope of a current drop value and that of a current peak value will respectively be sinusoidal waves.

Description

【発明の詳細な説明】 〔産業上の利用分野〕 本発明は入力電流を近似的に正弦波化することにより、
入力端子の高調波成分の低減と力率の教具を行いあわせ
て制御された出力電圧を得ることのできる直流電源!J
置に関する。
[Detailed Description of the Invention] [Industrial Application Field] The present invention transforms the input current into an approximate sine wave, thereby
A DC power supply that can obtain a controlled output voltage by reducing the harmonic components of the input terminal and using a power factor tool! J
Regarding location.

〔従来の技術〕[Conventional technology]

交流電源より直流出力を得る直流電源装置としては、単
に整流器を用いただけでは、入力電流波形が断続的で力
率と効率が低く好ましくない。そのため入力電流を近似
的に正弦波化することにより、入力端子の高調波成分の
低減と力率の改善を行う直流電源装置が知られており1
例えば第3図に示すようなものがある。この図に従って
説明すると、入力端子10.11より入力交流電圧を受
けて。
For a DC power supply device that obtains DC output from an AC power supply, simply using a rectifier is not preferable because the input current waveform is intermittent and the power factor and efficiency are low. Therefore, a DC power supply device is known that reduces harmonic components at the input terminal and improves the power factor by converting the input current into an approximate sine wave.
For example, there is one shown in FIG. To explain according to this diagram, input AC voltage is received from input terminals 10 and 11.

ラインフィルタ14を介して整流回路2により脈流を得
る。この脈流電圧はチョークコイル3Iを介してスイッ
チ素子4に接続される。このスイッチ1子4はオンオフ
を繰り返してオフの時にチロ−クコイル31のエネルギ
ーがフライホイールダイオード5を介して出力端子12
.13へ送られ、負荷1?Lに直流出力電圧が発生する
A pulsating current is obtained by the rectifier circuit 2 via the line filter 14. This pulsating voltage is connected to the switch element 4 via the choke coil 3I. This switch 1 element 4 repeatedly turns on and off, and when it is off, the energy of the chiroke coil 31 is transferred to the output terminal 12 via the flywheel diode 5.
.. Sent to 13, load 1? A DC output voltage is generated at L.

ここで脈tIL′fIi圧は抵抗5R1,R2により分
圧された値υiと出力電圧と基準電圧源16との誤差を
誤差増幅56により増幅した値υ0を乗算57により基
準正弦波電圧Vrとして取り出す、この基準正弦波電圧
Vrは負荷状態によって振幅v4御ができ、エネルギー
の制御を可能にしている0次に抵抗5R3によって検出
されるスイッチ素子4の電流比例値層、をコンパレータ
8により前記基準正弦波電圧V「と比較し、電流比例値
υt4が基準正弦波電圧ν「に達するとスイッチ素子4
の駆動を遮断する。チョークコイル31のエネルギーが
放出さ九るとコイル電圧がゼロとなる。その状態をチロ
−クコイル31の二次検出巻線で検出し、9!動段内の
フリップフロップ回路9を動作させ、スイッチ素子4を
駆動する。このようなスイッチ素子4のスイッチングに
より入力端子を第4図にその半サイクルを示すように三
角波形とし、ピーク値の包絡線を正弦波とする0入力交
流電流の波形は高周波三角波であるが、ラインフィルタ
14により変調周波数成分を減衰することにより正弦波
形となる。
Here, the pulse tIL'fIi pressure is obtained by multiplying 57 by the value υ0 obtained by amplifying the error between the value υi divided by the resistors 5R1 and R2, the output voltage, and the reference voltage source 16 by the error amplifier 56, as the reference sine wave voltage Vr. , this reference sine wave voltage Vr can be controlled in amplitude v4 depending on the load condition, and the current proportional value layer of the switching element 4 detected by the zero-order resistor 5R3, which enables energy control, is converted to the reference sine wave voltage by a comparator 8. When the current proportional value υt4 reaches the reference sine wave voltage ν, the switching element 4
cut off the drive. When the energy of the choke coil 31 is released, the coil voltage becomes zero. The state is detected by the secondary detection winding of the Chiroku coil 31, and 9! The flip-flop circuit 9 in the dynamic stage is operated to drive the switch element 4. By switching the switch element 4 in this manner, the input terminal is shaped into a triangular waveform as shown in FIG. 4, a half cycle of which is shown.The waveform of the 0-input alternating current is a high-frequency triangular wave, with the envelope of the peak value being a sine wave. A sinusoidal waveform is obtained by attenuating the modulated frequency component by the line filter 14.

〔発明が解決しようとするtsm〕[TSM that the invention aims to solve]

しかしながら、このような従来の直流電源装置にあって
はチョークコイルの電流は各スイッチングサイクル毎に
電流値ゼロからピーク値までの三角波となるためチョー
クコイル電流、スイッチ素子の電流、フライホイールダ
イオードの電流それぞれのピーク値が交流入力電流11
に比較して大きくなり、スイッチング損失の増大やtl
fP発生の増大という問題があった。
However, in such a conventional DC power supply, the current in the choke coil becomes a triangular wave from zero to the peak value in each switching cycle, so the choke coil current, switch element current, and flywheel diode current Each peak value is AC input current 11
This increases switching loss and tl
There was a problem of increased occurrence of fP.

〔課題を解決するための手段〕[Means to solve the problem]

本発明では5以上のべた問題点を解決するため。 The present invention aims to solve five or more problems.

負荷の電圧の比例値と基準電圧との差電圧を得る手段と
5入力交流電源の電圧の絶対値の比例値との乗算手段を
備えて、主回路のチョークコイルの電流の絶対値の比例
値と前記の乗算信゛号とを履歴特性を有する電圧比較器
により主回路のスイッチング素子を駆動するものである
A means for obtaining a differential voltage between a proportional value of the voltage of the load and a reference voltage, and a means for multiplying by a proportional value of the absolute value of the voltage of the 5-input AC power supply, and a proportional value of the absolute value of the current of the choke coil of the main circuit is provided. and the above-mentioned multiplication signal are used to drive the switching elements of the main circuit using a voltage comparator having a history characteristic.

〔作用〕[Effect]

したがって5負荷の電圧の比例値と基準電圧との差電圧
を得る手段により、所望の出力設定値に対応する制御信
号が得られる。ついで入力交流電飾の電圧の絶対値の比
例値との乗算手段により。
Therefore, by means of obtaining the difference voltage between the proportional value of the voltage of the five loads and the reference voltage, a control signal corresponding to a desired output setting value can be obtained. Then, by means of multiplying the absolute value of the voltage of the input AC illumination by a proportional value.

振幅制御できる基準の正弦波電圧が得られる。そして、
主回路のチロ−クコイルの電流の大きさに比例した電圧
をその基準正弦波電圧とを比較し。
A reference sine wave voltage whose amplitude can be controlled is obtained. and,
Compare the voltage proportional to the current magnitude of the Chirok coil in the main circuit with its reference sine wave voltage.

その基準正弦波電圧にほぼ比例した履歴幅を持つ電圧比
較器でチョークコイルの電流変化幅をその履歴幅の中に
制限するように主回路のスイッチング素子を駆動するも
のである。
A voltage comparator having a hysteresis width approximately proportional to the reference sine wave voltage drives the switching element of the main circuit so as to limit the current variation width of the choke coil within the hysteresis width.

〔実施例〕〔Example〕

第1図は本発明に係る直流型m装置の一実施例の接続図
である。同図において、入力端子10.11より入力交
流電圧を受けて、ラインフィルタ14を介して整流回路
2により脈流電圧を得る。この脈流電圧はチョークコイ
ル3を介してスイッチ素子4に接続される。このスイッ
チ素子4は入力交流の周波数に比べてはるかに高い周波
数でオンオフを繰り返す、オンの時にチョークコイル3
にエネルギーをEえて、オフの時にチョークコイル3の
エネルギーがフライホイールダイオード5を介して出力
端子12.13へ送られ、負荷RLに直流出力電圧を発
生させる。出力端子12.13に並列接続されたコンデ
ンサC1はスイッチング周波数に対して平滑作用をする
FIG. 1 is a connection diagram of an embodiment of the DC type m device according to the present invention. In the figure, an input AC voltage is received from an input terminal 10.11, and a pulsating voltage is obtained by a rectifier circuit 2 via a line filter 14. This pulsating voltage is connected to a switch element 4 via a choke coil 3. This switching element 4 repeats on and off at a frequency much higher than the frequency of the input AC, and when it is on, the choke coil 3
When the choke coil 3 is off, the energy of the choke coil 3 is sent to the output terminal 12.13 via the flywheel diode 5, generating a DC output voltage at the load RL. A capacitor C1 connected in parallel to the output terminals 12,13 has a smoothing effect on the switching frequency.

ここで整流回路2の出力である脈流電圧は抵抗raρ1
.l?2により分圧された値υ1と出力電圧と基準電圧
源16との誤差を誤差増幅S6により増幅した値υ0を
乗算器7により基準正弦波電圧Vrとして取り出す、こ
の基準正弦波電圧Vrは負荷状態によって振幅制御がで
き、エネルギーの1s御を可能にしている0次に変流器
1によって検出される入力文流電*liの比例値を整流
回路15を介してその絶対値を得て、抵抗器126の両
端にその対応する電圧υ11を発生させる。
Here, the pulsating voltage that is the output of the rectifier circuit 2 is generated by the resistance raρ1
.. l? The value υ0 obtained by amplifying the error between the value υ1 divided by 2, the output voltage, and the reference voltage source 16 by the error amplification S6 is extracted as the reference sine wave voltage Vr by the multiplier 7. This reference sine wave voltage Vr is set in the load state. The proportional value of the input current current*li detected by the zero-order current transformer 1 is obtained through the rectifier circuit 15 to obtain its absolute value, and the absolute value is obtained through the rectifier circuit 15. A corresponding voltage υ11 is generated across the device 126.

この電圧値を抵抗器R7,R8,R9とコンパレータ8
により交流入力電圧値υ1にほぼ比例したヒステリシス
幅を作り、そのヒステリシス幅の中でのしきい値におい
て駆動出力信号を遷移する。すなわちコンパレータ8に
より前記の基準正弦波電圧Vrと比較し2例えば第2図
に示すようにt=tlで電流比例値V目が基準正弦波電
圧Vrに達するとスイッチ素子4の駆動を行い、 t=
t2で電流比例値vt+が基準正弦波電圧Vrに達する
とスイッチ素子4の駆動を遮断する。スイッチ素子4が
オンしている区間ではチョークコイル3にエネルギーが
蓄積され。
This voltage value is connected to resistors R7, R8, R9 and comparator 8.
Thus, a hysteresis width approximately proportional to the AC input voltage value υ1 is created, and the drive output signal transitions at a threshold within the hysteresis width. That is, the comparator 8 compares it with the reference sine wave voltage Vr, and when the current proportional value V reaches the reference sine wave voltage Vr at t=tl, for example, as shown in FIG. 2, the switching element 4 is driven. =
When the current proportional value vt+ reaches the reference sine wave voltage Vr at t2, the driving of the switching element 4 is cut off. Energy is accumulated in the choke coil 3 in the section where the switch element 4 is on.

スイッチ素子4がオフするとチョークコイル3にa碩さ
れたエネルギーはフライホイールダイオード5を介して
負荷RLに放出供給される。
When the switch element 4 is turned off, the energy applied to the choke coil 3 is released and supplied to the load RL via the flywheel diode 5.

このようなスイッチ素子4のスイッチングにより入力端
子波形を高周波三角波形の連続とし、′R流降下値の包
絡線と電流ピーク値の包絡線はそれぞれ正弦波となる。
By switching the switch element 4 in this manner, the input terminal waveform becomes a continuous high-frequency triangular waveform, and the envelope of the 'R current drop value and the envelope of the current peak value each become a sine wave.

したがって、交流入力波形の谷点に対応するt=0. 
t=7/2の付近のスイッチング周波数はその波形の頂
点t= t2付近のスイッチング周波数と比較して高く
なる。
Therefore, t=0. which corresponds to the valley point of the AC input waveform.
The switching frequency near t=7/2 is higher than the switching frequency near the peak of the waveform, t=t2.

入力交流電流1iの平均値は各サイクルの波形は三角波
であるからピーク値の172となり、正弦波形となり1
入力のフィルタにより変調周波数成分を減衰することに
より高周波成分を減少させて力率の改善も図っている。
Since the waveform of each cycle is a triangular wave, the average value of the input AC current 1i is the peak value of 172, which is a sine waveform, and is 1
By attenuating the modulation frequency component using an input filter, the high frequency component is reduced and the power factor is also improved.

抵FXSR9の値が抵抗器R1,R8の値に比較して充
分大きい場合は以上述べたようなヒステリシスの形とな
るが、抵抗i!SR9の値が小さくなると第2図の波形
におけるヒステリシスの幅が入力交流電圧波形との比例
が(ずれて、−様の幅に近づく、この場合は、交流入力
波形の谷点に対応する【・0.t・丁/2の付近のスイ
ッチング周波数とその波形の頂点L= 12付近のスイ
ッチング周波数とは同一に近くなる。
If the value of the resistor FXSR9 is sufficiently large compared to the values of the resistors R1 and R8, the above-mentioned hysteresis will occur, but the resistor i! As the value of SR9 becomes smaller, the width of the hysteresis in the waveform shown in Figure 2 becomes proportional to the input AC voltage waveform. The switching frequency near 0.t·d/2 and the switching frequency near the peak L=12 of the waveform are close to the same.

を流検出手段としては変流Diに限らず、チロ−クコイ
ル3の電流を検出できれば他の方法でもよい6例えばチ
オ−クコイル3に直列に低抵抗を挿入する方法でもよい
。また、チョークコイル3の電流■3はスイッチ素子4
の電流14とフライホイールダイオード5の電流■5の
和であるので、チョークコイル3とスイッチ素子4との
それぞれに直流変流器あるいは低抵抗を挿入してそれら
の信号を加算する方法でもよい。
The current detection means is not limited to the current transformation Di, but any other method may be used as long as the current in the choke coil 3 can be detected.For example, a method of inserting a low resistance in series with the choke coil 3 may be used. In addition, the current ■3 of the choke coil 3 is connected to the switch element 4.
Since the current 14 is the sum of the current 14 of the flywheel diode 5 and the current 5 of the flywheel diode 5, a DC transformer or a low resistance may be inserted into each of the choke coil 3 and the switch element 4 and their signals may be added.

また電圧検出手段としては、入力端子10.11から直
接M流口路を介して得ることもできる。その場合は絶縁
手段として小型変圧器あるいは光結合素子を間に挿入す
る必要がある。
The voltage detection means can also be obtained directly from the input terminal 10.11 via the M flow path. In that case, it is necessary to insert a small transformer or an optical coupling element between them as an insulating means.

第1図に示す回路図は一実施例であって、整流回路2と
スイッチ素子4とフライホイールダイオード5とのそれ
ぞれの極性を入れ換えることにより同様の作用をする。
The circuit diagram shown in FIG. 1 is one embodiment, and the same effect can be achieved by switching the polarities of the rectifying circuit 2, the switching element 4, and the flywheel diode 5.

そしてフライホイールダイオード5は一方向性スイッチ
ング素子であれば。
And if the flywheel diode 5 is a unidirectional switching element.

通常のダイオードに限らず、シ碧ットキーダイオードで
もよく、スイッチ素子4としては電界効果トランジスタ
、バイポーラトランジスタ、 IGBT等が使える。
In addition to a normal diode, a Schottky diode may be used, and the switch element 4 may be a field effect transistor, a bipolar transistor, an IGBT, or the like.

〔発明の効果〕〔Effect of the invention〕

本発明は以上述べたような特徴を有しているので、直流
電源装置においてスイッチ素子、チタークコイル、フラ
イホイールダイオードや入力ラインフィルタの実効電流
とdi/dtが小さくなり、各損失が低下し2発生雑音
も小さくなり、力率、効率が向1するいう効果が得られ
る。そして各無効電力が減少するので、主回路部品の定
格を低下でき、経済的である。
Since the present invention has the above-mentioned features, the effective current and di/dt of the switching element, Chittark coil, flywheel diode, and input line filter in the DC power supply device are reduced, and each loss is reduced. Noise is also reduced, and the power factor and efficiency are improved. Since each reactive power is reduced, the rating of the main circuit components can be lowered, which is economical.

【図面の簡単な説明】[Brief explanation of the drawing]

第1図は本発明に係る直流電源装置の実施例を示し、f
I42図は第1図に示す装置の動作を説明するための各
部の波形図を示し、第3図は従来の直I11電源装置の
回路図を示し、第4図は第3図に示す回路の動作波形を
示す。 l・・・変ml       2・・・整流回路3・・
・チョークコイル、  4・・・スイッチ素子5・・・
フライホイールダイオード 6・・・誤差増幅器、7・・・乗算器、8・・・コンパ
レータ9・・・フリップフロップ回路 10、ll・・・入力端子 12.13・・・出力端子
14・・・ラインフィルタ、  15・・・整流回路1
G・・・基準電圧源5 CI・・・コンデンサ [1l−R9・・・抵抗器。 RL・・・負荷
FIG. 1 shows an embodiment of the DC power supply device according to the present invention, and f
Figure I42 shows a waveform diagram of each part to explain the operation of the device shown in Figure 1, Figure 3 shows a circuit diagram of a conventional direct I11 power supply, and Figure 4 shows a diagram of the circuit shown in Figure 3. The operating waveforms are shown. l...variable ml 2...rectifier circuit 3...
・Choke coil, 4... Switch element 5...
Flywheel diode 6...error amplifier, 7...multiplier, 8...comparator 9...flip-flop circuit 10, ll...input terminal 12.13...output terminal 14...line Filter, 15... Rectifier circuit 1
G... Reference voltage source 5 CI... Capacitor [1l-R9... Resistor. RL...Load

Claims (1)

【特許請求の範囲】 入力交流電源に接続された両波整流器、該両波整流器の
出力に接続されたチョークコイル、該チョークコイルに
スイッチング素子を接続するともに、前記チョークコイ
ルに一方向性スイッチング素子を介して負荷に直流電力
を供給する直流電源装置において、 前記負荷の電圧の比例値と基準電圧との差電圧と、前記
入力交流電源の電圧の絶対値の比例値との乗算手段を備
えて、前記チョークコイルの電流の絶対値の比例値と前
記乗算信号とを履歴特性を有する電圧比較器により前記
スイッチング素子を駆動することを特徴とする直流電源
装置。
[Claims] A double-wave rectifier connected to an input AC power supply, a choke coil connected to the output of the double-wave rectifier, a switching element connected to the choke coil, and a unidirectional switching element connected to the choke coil. A DC power supply device that supplies DC power to a load via a DC power source, comprising means for multiplying a difference voltage between a proportional value of the voltage of the load and a reference voltage by a proportional value of the absolute value of the voltage of the input AC power supply. , wherein the switching element is driven by a voltage comparator having a history characteristic between a proportional value of the absolute value of the current of the choke coil and the multiplication signal.
JP23397088A 1988-09-19 1988-09-19 Dc power device Pending JPH0284069A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP23397088A JPH0284069A (en) 1988-09-19 1988-09-19 Dc power device

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP23397088A JPH0284069A (en) 1988-09-19 1988-09-19 Dc power device

Publications (1)

Publication Number Publication Date
JPH0284069A true JPH0284069A (en) 1990-03-26

Family

ID=16963492

Family Applications (1)

Application Number Title Priority Date Filing Date
JP23397088A Pending JPH0284069A (en) 1988-09-19 1988-09-19 Dc power device

Country Status (1)

Country Link
JP (1) JPH0284069A (en)

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH0442779A (en) * 1990-06-05 1992-02-13 Sanken Electric Co Ltd Power unit
JPH0421192U (en) * 1990-06-12 1992-02-21
JPH0425481U (en) * 1990-06-20 1992-02-28
JPH04168975A (en) * 1990-11-01 1992-06-17 Fuji Elelctrochem Co Ltd Power supply device
JPH0698536A (en) * 1992-07-03 1994-04-08 Samsung Electron Co Ltd Correction circuit of power factor
EP0600809A1 (en) * 1992-11-30 1994-06-08 ALPES TECHNOLOGIES (société anonyme) AC dynamic compensator
JPH06197558A (en) * 1992-08-25 1994-07-15 General Electric Co <Ge> Power source circuit with power factor correction function
JP2010022125A (en) * 2008-07-10 2010-01-28 Cosel Co Ltd Multi-phase power-factor improving circuit
WO2010106701A1 (en) * 2009-03-18 2010-09-23 株式会社村田製作所 Pfc converter
JP2012182867A (en) * 2011-02-28 2012-09-20 Denso Corp Power supply unit

Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH0442779A (en) * 1990-06-05 1992-02-13 Sanken Electric Co Ltd Power unit
JPH0421192U (en) * 1990-06-12 1992-02-21
JPH0425481U (en) * 1990-06-20 1992-02-28
JPH04168975A (en) * 1990-11-01 1992-06-17 Fuji Elelctrochem Co Ltd Power supply device
JPH0698536A (en) * 1992-07-03 1994-04-08 Samsung Electron Co Ltd Correction circuit of power factor
JPH06197558A (en) * 1992-08-25 1994-07-15 General Electric Co <Ge> Power source circuit with power factor correction function
EP0600809A1 (en) * 1992-11-30 1994-06-08 ALPES TECHNOLOGIES (société anonyme) AC dynamic compensator
JP2010022125A (en) * 2008-07-10 2010-01-28 Cosel Co Ltd Multi-phase power-factor improving circuit
WO2010106701A1 (en) * 2009-03-18 2010-09-23 株式会社村田製作所 Pfc converter
JP5104946B2 (en) * 2009-03-18 2012-12-19 株式会社村田製作所 PFC converter
US8427853B2 (en) 2009-03-18 2013-04-23 Murata Manufacturing Co., Ltd. Power factor correction converter including operation mode determination unit
JP2012182867A (en) * 2011-02-28 2012-09-20 Denso Corp Power supply unit

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