JP6805212B2 - Drive device and air conditioner for 3-set winding structure motor - Google Patents

Drive device and air conditioner for 3-set winding structure motor Download PDF

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JP6805212B2
JP6805212B2 JP2018157321A JP2018157321A JP6805212B2 JP 6805212 B2 JP6805212 B2 JP 6805212B2 JP 2018157321 A JP2018157321 A JP 2018157321A JP 2018157321 A JP2018157321 A JP 2018157321A JP 6805212 B2 JP6805212 B2 JP 6805212B2
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佐理 前川
佐理 前川
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Description

本発明の実施形態は、３組巻線構造のモータを駆動する装置，及びその装置を備えた空気調和機に関する。 An embodiment of the present invention relates to a device for driving a motor having a three-set winding structure, and an air conditioner including the device.

例えば永久磁石同期モータ等の交流モータを駆動するには、インバータを用いて直流電源を３相交流電力に変換する必要がある。そして、このような駆動システムにおいて商用の３相交流電源を用いる場合は、３相交流電源から直流電力を得るための電源装置が搭載される。 For example, in order to drive an AC motor such as a permanent magnet synchronous motor, it is necessary to convert a DC power source into a three-phase AC power using an inverter. When a commercial three-phase AC power supply is used in such a drive system, a power supply device for obtaining DC power from the three-phase AC power supply is installed.

３相交流から直流を得る電源装置としては、例えば非特許文献１に記載されているダイオード整流回路と昇圧チョッパ回路とを用いる方式や、非特許文献２に記載されているＰＷＭ整流器を用いる方式等が一般的に知られている。ダイオード整流回路は、３相交流電圧を整流し直流電圧へ変換する。ダイオード整流器で整流された電圧は、交流電圧と同様に振幅が大きく変動するため、平滑コンデンサを接続して電圧を平滑する。図１７は、ダイオード整流器，インダクタ及び平滑コンデンサからなる電源装置に接続されるインバータを示す。 Examples of the power supply device that obtains direct current from three-phase AC include a method using a diode rectifier circuit and a step-up chopper circuit described in Non-Patent Document 1, a method using a PWM rectifier described in Non-Patent Document 2, and the like. Is generally known. The diode rectifier circuit rectifies the three-phase AC voltage and converts it into a DC voltage. Since the amplitude of the voltage rectified by the diode rectifier fluctuates greatly like the AC voltage, a smoothing capacitor is connected to smooth the voltage. FIG. 17 shows an inverter connected to a power supply device including a diode rectifier, an inductor and a smoothing capacitor.

このように、平滑コンデンサが接続された整流器のダイオードは、交流電圧が平滑コンデンサの端子電圧よりも大きい場合にのみ導通する。そのため、交流電源から整流器に流れ込む電流は、図１８に示すように、交流電圧のピーク付近でのみレベルが変位する力率の悪い波形となる。そこで、昇圧チョッパ回路をダイオード整流回路と平滑コンデンサとの間に接続して入力電流の高調波を低減し、得られた直流電源をインバータに供給する。 As described above, the diode of the rectifier to which the smoothing capacitor is connected conducts only when the AC voltage is larger than the terminal voltage of the smoothing capacitor. Therefore, as shown in FIG. 18, the current flowing from the AC power supply to the rectifier has a poor power factor waveform in which the level is displaced only near the peak of the AC voltage. Therefore, a boost chopper circuit is connected between the diode rectifier circuit and the smoothing capacitor to reduce the harmonics of the input current, and the obtained DC power supply is supplied to the inverter.

また、ＰＷＭ整流器を用いる方式では、リアクトルを介して３相交流を３相のブリッジ回路に供給する。そして、ブリッジ回路を構成するパワーデバイスによりスイッチングを行い、３相の交流電圧に同期した電圧を出力するよう動作させる。これにより正弦波状で低高調波の電流を通電して、高い力率で直流電圧への変換が実現できる。 Further, in the method using a PWM rectifier, three-phase alternating current is supplied to the three-phase bridge circuit via the reactor. Then, switching is performed by the power device constituting the bridge circuit, and the voltage is operated so as to output a voltage synchronized with the three-phase AC voltage. As a result, a sinusoidal, low-harmonic current can be energized and converted to a DC voltage with a high power factor.

一方、単相交流を電源とするモータ駆動方式として、非特許文献３に開示されているように、小容量のフィルムコンデンサと単相ダイオード整流回路，及びインバータを用いた電解コンデンサレスインバータが提案されている。この方式によれば、力率を制御するための回路等を用いることなく、高力率で低高調波の電力供給を実現できる。 On the other hand, as a motor drive system using single-phase AC as a power source, as disclosed in Non-Patent Document 3, an electrolytic capacitor-less inverter using a small-capacity film capacitor, a single-phase diode rectifier circuit, and an inverter has been proposed. ing. According to this method, it is possible to realize power supply with a high power factor and low harmonics without using a circuit or the like for controlling the power factor.

また、特許文献１には、３相のモータ巻線を２組持つ多巻線構造のモータが示されている。このような多巻線モータは、巻線を並列化し、２組であれば２台のインバータでそれぞれの３相巻線に電流を通電することで電流を低減できる。また、２組の巻線の位相を構造的にずらすことで、互いの巻線により発生するトルクの脈動をキャンセルさせて、低振動のモータを実現することができる。 Further, Patent Document 1 discloses a motor having a multi-winding structure having two sets of three-phase motor windings. In such a multi-winding motor, the current can be reduced by parallelizing the windings and, if there are two sets, applying a current to each of the three-phase windings by two inverters. Further, by structurally shifting the phases of the two sets of windings, the pulsation of torque generated by the windings of each other can be canceled, and a low-vibration motor can be realized.

20th Annual IEEE Power Electronics Specialists Conference,pp58-66 Vol.1 “An active power factor correction technique for three-phase diode rectifiers”20th Annual IEEE Power Electronics Specialists Conference, pp58-66 Vol.1 “An active power factor correction technique for three-phase diode rectifiers” 電気学会論文誌D,Vol.114,No.12「電源電圧センサレス三相PWMインバータの一方式」IEEJ Transactions on D, Vol.114, No.12 "One method of power supply voltage sensorless three-phase PWM inverter" 平成12年電気学会全国大会論文集「高入力力率のダイオード整流回路を持つPMモータのインバータ制御法」2000 IEEJ National Convention Proceedings "Inverter control method for PM motors with diode rectifier circuit with high input power factor"

特開平４−３２５８９３号公報Japanese Unexamined Patent Publication No. 4-325893

しかしながら、３相のダイオード整流回路を用いる構成では、３相交流電源から直流側に電流が流れない期間が必ず存在するため、高調波の低減には限界がある。また、ＰＷＭ整流器を用いる構成は低高調波を実現することができるが、大容量のパワーデバイス，３相のリアクトル及び平滑コンデンサが必要となるため、回路が大型化してコスト増を招く。また、非特許文献３の電解コンデンサレスインバータは、力率制御回路なしで低高調波が実現できるが、モータのトルクを電源周波数の２倍周波数で変動させるため、大きなトルク脈動による振動や騒音等が問題となる。 However, in a configuration using a three-phase diode rectifier circuit, there is always a period during which no current flows from the three-phase AC power supply to the DC side, so there is a limit to the reduction of harmonics. Further, although a configuration using a PWM rectifier can realize low harmonics, a large-capacity power device, a three-phase reactor, and a smoothing capacitor are required, so that the circuit becomes large and the cost increases. Further, the electrolytic condenserless inverter of Non-Patent Document 3 can realize low harmonics without a power factor control circuit, but since the torque of the motor fluctuates at a frequency twice the power supply frequency, vibration and noise due to large torque pulsation, etc. Is a problem.

特許文献１の多巻線モータは、電流低減・低トルク脈動などメリットが多いが、交流電源から直流電圧を生成するためには、別途非特許文献１，２に開示されているような変換器が必要である。したがって、モータを駆動するために２組以上のインバータを用いることも併せると、システム全体のコストが増加する可能性があることが課題である。
そこで、比較的低コストな構成によって低高調波を実現できる３組巻線構造モータの駆動装置及び空気調和機を提供する。 The multi-winding motor of Patent Document 1 has many merits such as current reduction and low torque pulsation, but in order to generate a DC voltage from an AC power supply, a converter as separately disclosed in Non-Patent Documents 1 and 2 is required. Therefore, there is a problem that the cost of the entire system may increase when two or more sets of inverters are used to drive the motor.
Therefore, we provide a drive device and an air conditioner for a three-set winding structure motor that can realize low harmonics with a relatively low cost configuration.

実施形態の３組巻線構造モータの駆動装置は、それぞれが独立した３組の３相巻線を備え、９個の巻線端子を有する３組巻線構造モータを駆動対象とするもので、
３相交流電源の第１相と第２相との間の第１相間交流電圧，第２相と第３相との間の第２相間交流電圧，第３相と第１相との間の第３相間交流電圧を、それぞれ直流に変換する第１〜第３交流直流変換回路と、
前記第１交流直流変換回路の正側端子及び負側端子と、前記モータの第１組の３相巻線端子との間に接続される第１インバータと、
前記第２交流直流変換回路の正側端子及び負側端子と、前記モータの第２組の３相巻線端子との間に接続される第２インバータと、
前記第３交流直流変換回路の正側端子及び負側端子と、前記モータの第３組の３相巻線端子との間に接続される第３インバータと、
３相交流電源の３相の位相又は３相間の位相を検出する第１〜第３位相検出部と、
前記モータの第１組〜第３組の３相巻線端子にそれぞれ流れる電流を検出する第１〜第３電流検出部と、
前記モータのロータ回転位置を検出する位置検出部と、
前記モータの第１組の３相巻線に流れる電流を、前記第１インバータにより前記第１相間交流電圧に同期して制御し、
前記モータの第２組の３相巻線に流れる電流を、前記第２インバータにより前記第２相間交流電圧に同期して制御し、
前記モータの第３組の３相巻線に流れる電流を、前記第３インバータにより前記第３相間交流電圧に同期して制御する制御部とを備える。
前記制御部は、前記ロータ回転位置及び前記第１〜第３電流検出部により検出された電流に基づいてベクトル制御を行う際に用いるｑ軸電流指令値を、速度指令値と前記モータの速度との差に基づく速度制御の結果に、前記交流電源の周波数の２倍値に関連した演算パラメータを乗じて生成する。 The drive device for the three-set winding structure motor of the embodiment is intended to drive a three-set winding structure motor each having three independent sets of three-phase windings and having nine winding terminals.
The first-phase AC voltage between the first and second phases of a three-phase AC power supply, the second-phase AC voltage between the second and third phases, and the third-phase and first-phase The first to third AC / DC conversion circuits that convert the AC voltage between the third phases to DC, respectively.
A first inverter connected between the positive and negative terminals of the first AC / DC conversion circuit and the three-phase winding terminal of the first set of the motor.
A second inverter connected between the positive and negative terminals of the second AC / DC conversion circuit and the second set of three-phase winding terminals of the motor.
A third inverter connected between the positive and negative terminals of the third AC / DC conversion circuit and the third set of three-phase winding terminals of the motor.
The first to third phase detectors that detect the phase of the three phases of a three-phase AC power supply or the phase between the three phases,
The first to third current detection units that detect the current flowing through the three-phase winding terminals of the first to third sets of the motor, respectively.
A position detection unit that detects the rotor rotation position of the motor, and
The current flowing through the first set of three-phase windings of the motor is controlled by the first inverter in synchronization with the first-phase AC voltage.
The current flowing through the second set of three-phase windings of the motor is controlled by the second inverter in synchronization with the second-phase AC voltage.
The motor includes a control unit that controls the current flowing through the third set of three-phase windings of the motor in synchronization with the third-phase AC voltage by the third inverter.
The control unit uses the speed command value and the speed of the motor as the q-axis current command value used when performing vector control based on the rotor rotation position and the current detected by the first to third current detection units. Is generated by multiplying the result of speed control based on the difference between the above and the calculation parameters related to the double value of the frequency of the AC power supply.

また、実施形態の空気調和機は、それぞれが独立した３組の３相巻線を備え、９個の巻線端子を有する３組巻線構造モータと、
このモータを駆動する本実施形態の３組巻線構造モータの駆動装置と、
前記モータを介して駆動される圧縮機とを備える。 Further, the air conditioner of the embodiment includes a three-set winding structure motor each having three sets of independent three-phase windings and having nine winding terminals.
The drive device of the three-set winding structure motor of the present embodiment that drives this motor,
It includes a compressor driven via the motor.

第１実施形態であり、３組巻線構造モータを駆動するシステムの構成を示す図The figure which shows the structure of the system which drives 3 sets winding structure motor which is 1st Embodiment. 制御部の構成を要部について示す機能ブロック図Functional block diagram showing the configuration of the control unit for the main parts ３相交流電源のＵＶ相電圧波形を示す図The figure which shows the UV phase voltage waveform of a three-phase AC power source. 第１インバータに供給される直流電圧ＶDC1の波形を示す図The figure which shows the waveform of the DC voltage VDC1 supplied to the 1st inverter 第１インバータのｑ軸電流Ｉｑ１の波形を示す図The figure which shows the waveform of the q-axis current Iq1 of the 1st inverter 第１〜第３巻線のトルクＴｍ１〜Ｔｍ３及び合計トルクＴallの波形を示す図The figure which shows the waveform of the torque Tm1 to Tm3 and the total torque Tall of the 1st to 3rd windings. 第１〜第３インバータに供給される直流電圧ＶDC1，ＶDC2，ＶDC3の波形を示す図The figure which shows the waveform of the DC voltage VDC1, VDC2, and VDC3 supplied to the 1st to 3rd inverters. 第１巻線の３相電流Ｉｕ１，Ｉｖ１，Ｉｗ１の波形を示す図The figure which shows the waveform of the three-phase current Iu1, Iv1, Iw1 of the 1st winding. 第１〜第３インバータのｑ軸電流Ｉｑ１〜Ｉｑ３の波形を示す図The figure which shows the waveform of the q-axis current Iq1 to Iq3 of the 1st to 3rd inverters 第１〜第３巻線のトルクＴｍ１〜Ｔｍ３及び合計トルクＴallの波形を示す図The figure which shows the waveform of the torque Tm1 to Tm3 and the total torque Tall of the 1st to 3rd windings. モータの回転速度ωを示す図The figure which shows the rotation speed ω of a motor モータの回転角度θを示す図The figure which shows the rotation angle θ of a motor ＵＶ，ＶＷ，ＷＵの各相間を流れる電源電流ＩAC1，ＩAC2，ＩAC3の波形を示す図The figure which shows the waveform of the power supply currents IAC1, IAC2, and IAC3 flowing between each phase of UV, VW, and WU. 電源系統のＵ，Ｖ，Ｗ相電流ＩACu，ＩACv，ＩACwの波形を示す図The figure which shows the waveform of the U, V, W phase current IACu, IACv, IACw of the power system 第２実施形態であり、第１〜第３制御部の構成を示す機能ブロック図A functional block diagram according to a second embodiment and showing the configurations of the first to third control units. 第３実施形態であり、３組巻線構造モータを駆動するシステムを適用した空気調和機の構成を示す機能ブロック図A functional block diagram showing a configuration of an air conditioner to which a system for driving a three-set winding structure motor is applied according to a third embodiment. 従来技術であり、ダイオード整流器，インダクタ及び平滑コンデンサからなる電源装置に接続されるインバータを示す図The figure which shows the inverter connected to the power-source device which is a prior art and consists of a diode rectifier, an inductor and a smoothing capacitor ３相交流電源の各相電流波形を示す図The figure which shows each phase current waveform of a three-phase AC power supply

（第１実施形態）
以下、第１実施形態について図１から図１４を参照して説明する。図１は、３組巻線構造モータを駆動するシステムの構成を示す。モータ１は、３相巻線２Ｕ，２Ｖ，２Ｗを３組備える多巻線モータであり、例えば永久磁石同期モータや誘導機などが想定されるが、本実施形態では永久磁石同期モータとする。モータ１は、３組の３相巻線端子（Ｕ１，Ｖ１，Ｗ１），（Ｕ２，Ｖ２，Ｗ２），（Ｕ３，Ｖ３，Ｗ３）を有している。 (First Embodiment)
Hereinafter, the first embodiment will be described with reference to FIGS. 1 to 14. FIG. 1 shows the configuration of a system for driving a three-set winding structure motor. The motor 1 is a multi-winding motor having three sets of three-phase windings 2U, 2V, and 2W. For example, a permanent magnet synchronous motor or an inducer is assumed, but in the present embodiment, it is a permanent magnet synchronous motor. The motor 1 has three sets of three-phase winding terminals (U1, V1, W1), (U2, V2, W2), and (U3, V3, W3).

３相交流電源３は、装置全体に電力を供給する電源であり、２００Ｖ又は４００Ｖ系である。整流回路４（１）〜４（３）はそれぞれ単相であり、ダイオードブリッジで構成されている。第１整流回路４（１）には、３相交流電源３のＵ，Ｖ相の交流が入力され、第２整流回路４（２）には同Ｖ，Ｗ相の交流が入力され、第３整流回路４（３）には同Ｗ，Ｕ相の交流が入力されている。 The three-phase AC power supply 3 is a power supply that supplies electric power to the entire device, and is a 200V or 400V system. Each of the rectifier circuits 4 (1) to 4 (3) is single-phase and is composed of a diode bridge. The U and V phase AC of the three-phase AC power supply 3 is input to the first rectifier circuit 4 (1), and the V and W phase AC is input to the second rectifier circuit 4 (2). The alternating current of the same W and U phases is input to the rectifier circuit 4 (3).

整流回路４（１）〜４（３）の直流出力端子間には、それぞれ小容量コンデンサ５（１）〜５（３）及び第１〜第３インバータ６（１）〜６（３）が並列に接続されている。小容量コンデンサ５は、例えば数μＦ〜数１０μＦ程度のフィルムコンデンサであり、インバータ６におけるスイッチングにより発生するリップルを平滑するために用いられる。電圧センサ２０（１）〜２０（３）は、それぞれコンデンサ５（１）〜５（３）の端子電圧ＶDC1〜ＶDC3を検出して制御部８に出力する。 Small-capacity capacitors 5 (1) to 5 (3) and first to third inverters 6 (1) to 6 (3) are connected in parallel between the DC output terminals of the rectifier circuits 4 (1) to 4 (3), respectively. It is connected to the. The small-capacity capacitor 5 is, for example, a film capacitor of about several μF to several tens of μF, and is used for smoothing the ripple generated by switching in the inverter 6. The voltage sensors 20 (1) to 20 (3) detect the terminal voltages VDC1 to VDC3 of the capacitors 5 (1) to 5 (3), respectively, and output them to the control unit 8.

インバータ６（１）〜６（３）は、それぞれ６つのスイッチング素子，例えばＮチャネルＭＯＳＦＥＴを３相ブリッジ接続して構成されている。第１インバータ６（１）の各相出力端子はモータ１の巻線端子Ｕ１，Ｖ１，Ｗ１に接続され、第２インバータ６（２）の各相出力端子は同巻線端子Ｕ２，Ｖ２，Ｗ２に接続され、第３インバータ６（３）の各相出力端子は同巻線端子Ｕ３，Ｖ３，Ｗ３に接続されている。 Each of the inverters 6 (1) to 6 (3) is configured by connecting six switching elements, for example, an N-channel MOSFET, with a three-phase bridge. Each phase output terminal of the first inverter 6 (1) is connected to the winding terminals U1, V1, W1 of the motor 1, and each phase output terminal of the second inverter 6 (2) is the same winding terminal U2, V2, W2. Each phase output terminal of the third inverter 6 (3) is connected to the winding terminals U3, V3, W3.

電流センサ７（１）〜７（３）は、それぞれモータ１の各組巻線に流れる相電流を検出して、制御部８に出力する。本実施形態では、電流センサ７を各組毎に３相分配置しているが、それぞれ２相ずつでも良い。また、電流センサ７に替えて、インバータ６の下側スイッチング素子のソースにそれぞれシャント抵抗を配置しても良い。 The current sensors 7 (1) to 7 (3) each detect the phase current flowing through each set winding of the motor 1 and output it to the control unit 8. In the present embodiment, the current sensors 7 are arranged for three phases in each set, but two phases may be provided for each. Further, instead of the current sensor 7, a shunt resistor may be arranged at the source of the lower switching element of the inverter 6.

電圧センサ９（１）〜９（３）は、３相交流電源３の電圧値を検出するセンサであり、検出信号を制御部８に出力する。本実施形態では、３相の相間電圧（Ｕ，Ｖ），（Ｖ，Ｗ），（Ｗ，Ｖ）を検出しているが、各相電圧を検出したり、又は各相間若しくは各相の位相のみを検出しても良い。位置センサ１０は、モータ１のロータ回転位置θ及び回転速度ωを検出するセンサであり、例えばエンコーダやレゾルバ等が用いられる。又は、電圧や電流から位置を推定するセンサレス構成としても良い。制御部８は、モータ１の各相電流，回転位置及び３相交流電源３の電圧から、各インバータ６（１）〜６（３）のスイッチング素子に与えるスイッチング信号を生成する。 The voltage sensors 9 (1) to 9 (3) are sensors that detect the voltage value of the three-phase AC power supply 3, and output the detection signal to the control unit 8. In the present embodiment, the three-phase interphase voltages (U, V), (V, W), and (W, V) are detected, but each phase voltage is detected, or the interphase or the phase of each phase is detected. Only may be detected. The position sensor 10 is a sensor that detects the rotor rotation position θ and the rotation speed ω of the motor 1, and for example, an encoder, a resolver, or the like is used. Alternatively, a sensorless configuration in which the position is estimated from voltage or current may be used. The control unit 8 generates a switching signal to be given to the switching elements of the inverters 6 (1) to 6 (3) from each phase current of the motor 1, the rotation position, and the voltage of the three-phase AC power supply 3.

図２は、制御部８の内部構成を示している。速度指令値ωrefは、外部から与えられる、又はシステムとしての指令値である。位置センサ１０で検出された速度ωは、速度指令値ωrefと共に速度制御部１１に入力され、速度制御部１１はｑ軸電流指令値ＩqRefを出力する。速度制御部１１は、ＰＩ制御器等で構成される。ｑ軸電流指令値ＩqRefには１／３が乗じられて、各インバータ６（１）〜６（３）の電流指令値ＩqRef_baseが生成される。 FIG. 2 shows the internal configuration of the control unit 8. The speed command value ωref is a command value given from the outside or as a system. The speed ω detected by the position sensor 10 is input to the speed control unit 11 together with the speed command value ωref, and the speed control unit 11 outputs the q-axis current command value IqRef. The speed control unit 11 is composed of a PI controller and the like. The q-axis current command value IqRef is multiplied by 1/3 to generate the current command values IqRef_base for each of the inverters 6 (1) to 6 (3).

位相検出部１２（１）は、３相交流電源３の相間電圧Ｖｕｖの位相θｕｖを検出する。この位相に基づいたｓｉｎ２θｕｖを乗算器１３（１）により電流指令値ＩqRef_baseに乗じることで、第１インバータ６（１）に対するｑ軸電流指令値ＩqRef1が決定される。本実施形態では、位相θｕｖからｓｉｎ２θｕｖを演算して乗じているが、例えばｓｉｎθｕｖの絶対値を演算して乗じても良い。 The phase detection unit 12 (1) detects the phase θuv of the phase voltage Vuv of the three-phase AC power supply 3. By multiplying the current command value IqRef_base by the multiplier 13 (1) by sin 2 θuv based on this phase, the q-axis current command value IqRef 1 for the first inverter 6 (1) is determined. In the present embodiment, sin 2 θuv is calculated and multiplied from the phase θuv, but for example, the absolute value of sin θuv may be calculated and multiplied.

座標変換部１４（１）は、３相電流Ｉｕ１，Ｉｖ１，Ｉｗ１を、位置センサ１０が検出した回転位置θにより座標変換してｄ，ｑ軸電流Ｉｄ１，Ｉｑ１を得る。電流制御部１５（１）は、インバータ６（１）のｄ，ｑ軸電流指令値ＩdRef1，ＩqRef1とｄ，ｑ軸電流Ｉｄ１，Ｉｑ１とに基づきｄ，ｑ軸電圧指令値Ｖｄ１，Ｖｑ１を演算する。電流制御部１５（１）は、速度制御部１１と同様にＰＩ制御器等で構成される。 The coordinate conversion unit 14 (1) coordinates the three-phase currents Iu1, Iv1, Iw1 with the rotation position θ detected by the position sensor 10 to obtain the d and q-axis currents Id1 and Iq1. The current control unit 15 (1) calculates d, q-axis voltage command values Vd1, Vq1 based on the d, q-axis current command values IdRef1, IqRef1 and d, q-axis currents Id1, Iq1 of the inverter 6 (1). .. The current control unit 15 (1) is composed of a PI controller or the like like the speed control unit 11.

変調制御部１６（１）は、Ｖｄ１，Ｖｑ１及びインバータ６（１）の直流電圧ＶＤＣ１，モータ１の回転位置θから、各相のスイッチング信号Ｕ＋１,Ｕ−１,Ｖ＋１,Ｖ−１,Ｗ＋１,Ｗ−１を生成する。尚、図２では省略的に示しているが、位相検出部１２，座標変換部１４、電流制御部１５，変調制御部１６が、インバータ６（２），６（３）にも対応して存在している。 The modulation control unit 16 (1) uses the switching signals U + 1, U-1, V + 1, V-1, W + 1, of each phase from the DC voltage VDC1 of the Vd1, Vq1 and the inverter 6 (1), and the rotation position θ of the motor 1. Generate W-1. Although not shown in FIG. 2, the phase detection unit 12, the coordinate conversion unit 14, the current control unit 15, and the modulation control unit 16 also exist corresponding to the inverters 6 (2) and 6 (3). doing.

次に、本実施形態の作用について説明する。先ず、３相交流電源３のＵＶ相間電圧が印加される整流回路４（１）〜インバータ６（１）〜第１巻線２Ｕ（１）〜２Ｗ（１）の駆動系について説明する。ＵＶ相電圧Ｖｕｖは、（１）式及び図３に示される交流電圧である。
Ｖｕｖ＝√２Ｖｓｉｎ（２πｆｔ） …（１） Next, the operation of this embodiment will be described. First, the drive system of the rectifier circuit 4 (1) to the inverter 6 (1) to the first winding 2U (1) to 2W (1) to which the UV-phase voltage of the three-phase AC power supply 3 is applied will be described. The UV phase voltage Vuv is the AC voltage shown in Eq. (1) and FIG.
Vuv = √2Vsin (2πft)… (1)

整流回路４（１）は全波整流を行う。小容量コンデンサ１の容量は数μＦ程度であるため、商用交流周波数の電圧変動を平滑するには不十分であり、インバータ６（１）の直流電圧ＶDC1は、（２）式及び図４に示すように０〜√２Ｖまで変動する電圧となり、２００Ｖ系であれば０〜２８０［Ｖ］である。尚、図４では電圧振幅を正規化して示している。
ＶDC1＝√２Ｖｓｉｎ２（２πｆｔ） …（２） The rectifier circuit 4 (1) performs full-wave rectification. Since the capacitance of the small-capacity capacitor 1 is about several μF, it is insufficient to smooth the voltage fluctuation of the commercial AC frequency, and the DC voltage VDC1 of the inverter 6 (1) is shown in the equation (2) and FIG. As described above, the voltage fluctuates from 0 to √2V, and in the case of a 200V system, it is 0 to 280 [V]. In FIG. 4, the voltage amplitude is normalized and shown.
VDC1 = √2Vsin 2 (2πft)… (2)

この脈動する電圧変動の位相に同期するように、位相検出部１２（１）で検出される位相θuvより得られるｓｉｎθuvの絶対値が乗じられるため、ｑ軸電流指令値ＩqRef1も直流電圧ＶDC1と同様に脈動する値となる。そして、この指令値の通りに第１巻線２Ｕ（１）〜２Ｗ（１）へのｑ軸電流Ｉｑ１が、脈動値として（３）式及び図５に示すように、通電される。
Ｉｑ１＝ＩｑRef＿base・ｓｉｎ２（２πｆｔ） …（３） Since the absolute value of sinθuv obtained from the phase θuv detected by the phase detection unit 12 (1) is multiplied so as to synchronize with the phase of this pulsating voltage fluctuation, the q-axis current command value IqRef1 is also the same as the DC voltage VDC1. It becomes a value that pulsates. Then, according to this command value, the q-axis current Iq1 to the first winding 2U (1) to 2W (1) is energized as a pulsation value as shown in the equation (3) and FIG.
Iq1 = IqRef_base · sin 2 (2πft)… (3)

この結果、第１巻線２Ｕ（１）〜２Ｗ（１）に流れる電流と回転子の永久磁石とにより発生するトルクＴｍ１は、（４）式に示すように、ＵＶ間電圧Ｖｕｖの２倍周波数に同期した脈動成分となる。
Ｔｍ１＝ＰφＩｑ１＝ＰφＩｑRef＿base・ｓｉｎ２（２πｆｔ）
＝ＰφＩｑRef＿base・｛１−ｃｏｓ（２・２πｆｔ）｝／２ …（４） As a result, the torque Tm1 generated by the current flowing in the first windings 2U (1) to 2W (1) and the permanent magnet of the rotor is twice the frequency of the UV-to-UV voltage Vuv as shown in equation (4). It becomes a pulsating component synchronized with.
Tm1 = PφIq1 = PφIqRef_base ・ sin 2 (2πft)
= PφIqRef_base ・ {1-cos (2.2πft)} / 2… (4)

また、モータ１の回転数ωｍを用いて第１巻線２Ｕ（１）〜２Ｗ（１）によるモータ１の出力電力Ｐｍ１を（５）式で表す。
Ｐｍ１＝ωｍＴｍ１
＝ωｍＰφＩｑRef＿base・｛１−ｃｏｓ（２・２πｆｔ）｝／２…（５） Further, the output power Pm1 of the motor 1 by the first windings 2U (1) to 2W (1) is expressed by the equation (5) using the rotation speed ωm of the motor 1.
Pm1 = ωmTm1
= ΩmPφIqRef_base ・ {1-cos (2.2πft)} / 2 ... (5)

（５）式は、交流電源３のＵＶ間からインバータ６（１）→第１巻線２Ｕ（１）〜２Ｗ（１）へと供給される電力が、（１）式で示すＵＶ間電圧Ｖｕｖに同期した成分であることを示している。また、交流電源３のＵＶ間より入力される電力Ｐin1は、整流回路４（１）に流れる電流ＩAC1から（６）式で表せる。
Ｐin1＝Ｖｕｖ・ＩAC1＝√２Ｖｓｉｎ（２πｆｔ）ＩAC1 …（６） In the formula (5), the power supplied from the UV of the AC power supply 3 to the inverter 6 (1) → the first winding 2U (1) to 2W (1) is the UV voltage Vuv represented by the formula (1). It shows that it is a component synchronized with. Further, the electric power Pin1 input from between the UVs of the AC power supply 3 can be expressed by the equation (6) from the current IAC1 flowing through the rectifier circuit 4 (1).
Pin1 = Vuv · IAC1 = √2Vsin (2πft) IAC1… (6)

ここで、入力電力Ｐin1から出力電力Ｐｍ１までの効率をηとすると、入出力間には大きな平滑コンデンサやリアクトルなどの平滑作用を成す素子がないので、ＩAC1は（７）式で表せる。
ＩAC1＝Ｐin1／Ｖｕｖ＝ηＰｍ１／｛√２Ｖｓｉｎ（２πｆｔ）｝
＝ηＰｍ１／｛√２Ｖｓｉｎ（２πｆｔ）｝
＝ηωｍＰφＩｑRef＿base・ｓｉｎ２（２πｆｔ）／｛√２Ｖｓｉｎ（２πｆｔ）｝
＝ηωｍＰφＩｑRef＿base・ｓｉｎ（２πｆｔ）／（√２Ｖ） …（７） Here, assuming that the efficiency from the input power Pin1 to the output power Pm1 is η, IAC1 can be expressed by the equation (7) because there is no smoothing element such as a large smoothing capacitor or reactor between the input and output.
IAC1 = Pin1 / Vuv = ηPm1 / {√2Vsin (2πft)}
= ΗPm1 / {√2Vsin (2πft)}
= ΗωmPφIqRef_base ・ sin 2 (2πft) / {√2Vsin (2πft)}
= ΗωmPφIqRef_base ・ sin (2πft) / (√2V)… (7)

すなわち、第１巻線２Ｕ（１）〜２Ｗ（１）のｑ軸電流Ｉｑ１をＵＶ間電圧Ｖｕｖに同期して制御することで、交流電源３のＵＶ間に流れる交流電流を、Ｖｕｖと同位相の正弦波電流にできる。これにより、力率制御回路やＰＷＭ整流器を用いることなく力率を向上させて電源電流の歪を低減し、電流に含まれる高調波を低減できる。 That is, by controlling the q-axis current Iq1 of the first winding 2U (1) to 2W (1) in synchronization with the UV voltage Vuv, the AC current flowing between the UVs of the AC power supply 3 is in phase with Vuv. Can be a sinusoidal current. As a result, the power factor can be improved, the distortion of the power supply current can be reduced, and the harmonics contained in the current can be reduced without using a power factor control circuit or a PWM rectifier.

ここで、３相交流電源３の残りの相に着目する。ＶＷ間，ＷＵ間の相間電圧は、（１）式と同様に（８）,（９）式となり、第２巻線２Ｕ（２）〜２Ｗ（２），第３巻線２Ｕ（３）〜２Ｗ（３）で発生するトルクＴｍ２,Ｔｍ３は、それぞれ（１０）式，（１１）式で表される。
Ｖｖｗ＝√２Ｖｓｉｎ（２πｆｔ＋２π／３） …（８）
Ｖｗｕ＝√２Ｖｓｉｎ（２πｆｔ−２π／３） …（９）
Ｔｍ２＝ＰφＩｑ２＝ＰφＩｑRef＿base・ｓｉｎ２（２πｆｔ＋２π／３）…（１０）
Ｔｍ３＝ＰφＩｑ３＝ＰφＩｑRef＿base・ｓｉｎ２（２πｆｔ−２π／３）…（１１） Here, attention is paid to the remaining phases of the three-phase AC power supply 3. The interphase voltage between VW and WU is (8), (9) as in equation (1), and the second winding 2U (2) to 2W (2) and the third winding 2U (3) to The torques Tm2 and Tm3 generated in 2W (3) are represented by the equations (10) and (11), respectively.
Vvw = √2Vsin (2πft + 2π / 3)… (8)
Vwoo = √2Vsin (2πft-2π / 3)… (9)
Tm2 = PφIq2 = PφIqRef_base · sin 2 (2πft + 2π / 3) ... (10)
Tm3 = PφIq3 = PφIqRef_base · sin 2 (2πft-2π / 3)… (11)

モータ１の３組巻線の合計トルクＴallは、Ｔｍ１，Ｔｍ２，Ｔｍ３の和であるから（１２）式で表され、互いに１２０度位相差のトルクの脈動成分がキャンセルされることがわかる。図６に各組巻線のトルクＴｍ１〜Ｔｍ３及び合計トルクＴallの波形を示す。
Ｔall＝Ｔｍ１＋Ｔｍ２＋Ｔｍ３＝３ＰφＩｑRef＿base …（１２）
この結果、モータ１の出力トルク及び回転速度には電源周波数の脈動が現れず、低振動・低騒音を実現できる。 Since the total torque Tall of the three sets of windings of the motor 1 is the sum of Tm1, Tm2, and Tm3, it is expressed by the equation (12), and it can be seen that the pulsating components of the torques having a phase difference of 120 degrees from each other are canceled. FIG. 6 shows the waveforms of the torques Tm1 to Tm3 and the total torque Tall of each set winding.
Tall = Tm1 + Tm2 + Tm3 = 3PφIqRef_base… (12)
As a result, pulsation of the power supply frequency does not appear in the output torque and the rotation speed of the motor 1, and low vibration and low noise can be realized.

図７から図１４は，本実施形態の構成による各部の動作結果を示している。図７は、インバータ６（１）〜６（３）に夫々供給される直流電圧ＶDC1，ＶDC2，ＶDC3であり、コンデンサ５が小容量であるため、電源系統位相に応じてゼロＶまで低下している。 7 to 14 show the operation results of each part according to the configuration of this embodiment. FIG. 7 shows DC voltages VDC1, VDC2, and VDC3 supplied to the inverters 6 (1) to 6 (3), respectively, and since the capacitor 5 has a small capacity, the voltage drops to zero V according to the phase of the power supply system. There is.

図８は、第１巻線２Ｕ（１）〜２Ｗ（１）の３相電流Ｉｕ１，Ｉｖ１，ＩＷ１であり、図９は、各巻線のｑ軸電流Ｉｑ１,Ｉｑ２,Ｉｑ３である。各巻線のq軸電流は、３相交流電圧の位相に同期して制御されていることが分かる。 FIG. 8 shows the three-phase currents Iu1, Iv1, IW1 of the first windings 2U (1) to 2W (1), and FIG. 9 shows the q-axis currents Iq1, Iq2, Iq3 of each winding. It can be seen that the q-axis current of each winding is controlled in synchronization with the phase of the three-phase AC voltage.

図１０は、負荷が一定の場合の各巻線の発生トルクＴｍ１，Ｔｍ２，Ｔｍ３及び合計トルクＴallである。各巻線に流れるｑ軸電流は脈動しているが、それに基づき発生する合計トルクＴallは、脈動が相殺されて消えている。図１１はモータの回転速度ω，図１２は回転角度θである。合計トルクＴallの変動は無いため、回転速度ωの脈動も発生していない。 FIG. 10 shows the generated torques Tm1, Tm2, Tm3 and the total torque Tall of each winding when the load is constant. The q-axis current flowing through each winding is pulsating, but the total torque Tall generated based on the pulsating current cancels out the pulsation and disappears. FIG. 11 shows the rotation speed ω of the motor, and FIG. 12 shows the rotation angle θ. Since there is no fluctuation in the total torque Tall, no pulsation at the rotation speed ω has occurred.

図１３は、ＵＶ，ＶＷ，ＷＵの各相間を流れる電源電流ＩAC1，ＩAC2，ＩAC3、図１４は電源系統のＵ，Ｖ，Ｗ相電流ＩACu，ＩACv，ＩACwである。多少の歪みが残っているが、リアクトルやＰＦＣ回路、ＰＷＭ整流器無しで低高調波の電源電流を流すことができている。 FIG. 13 shows the power supply currents IAC1, IAC2, and IAC3 flowing between the UV, VW, and WU phases, and FIG. 14 shows the U, V, and W phase currents IACu, IACv, and IACw of the power supply system. Although some distortion remains, it is possible to pass a low harmonic power supply current without a reactor, PFC circuit, or PWM rectifier.

以上のように本実施形態の駆動装置は、それぞれが独立した３組の３相巻線２Ｕ，２Ｖ，２Ｗを備え、９個の巻線端子を有する３組巻線構造モータ１を駆動対象とする。第１〜第３整流回路４（１）〜４（３）には、それぞれ３相交流電源３のＵＶ相間交流，ＶＷ相間交流，ＷＵ相交流が入力されて、直流に変換される。第１〜第３インバータ６（１）〜６（３）には、それぞれ第１〜第３整流回路４（１）〜４（３）及び小容量コンデンサ５（１）〜５（３）を介して直流電源が供給される。 As described above, the drive device of the present embodiment has three sets of three-phase windings 2U, 2V, and 2W, each of which is independent, and has a three-set winding structure motor 1 having nine winding terminals as a drive target. To do. UV-phase AC, VW-phase AC, and WU-phase AC of the three-phase AC power supply 3 are input to the first to third rectifier circuits 4 (1) to 4 (3), respectively, and converted into direct current. The first to third inverters 6 (1) to 6 (3) are connected to the first to third rectifier circuits 4 (1) to 4 (3) and the small capacitance capacitors 5 (1) to 5 (3), respectively. DC power is supplied.

位相検出部１２（１）〜１２（３）は、それぞれ３相交流電源３の相間ＵＶ，ＶＷ，ＷＶの位相を検出し、電流センサ７（１）〜７（３）は、それぞれモータ１の各組巻線に流れる相電流を検出して制御部８に出力する。制御部８は、モータ１の第１組の３相巻線２Ｕ（１）〜２Ｗ（１）に流れる電流を、第１インバータ６（１）によりＵＶ相間交流電圧に同期して制御し、第２組の３相巻線２Ｕ（２）〜２Ｗ（２）に流れる電流を、第２インバータ６（２）によりＶＷ相間交流電圧に同期して制御し、第３組の３相巻線２Ｕ（３）〜２Ｗ（３）に流れる電流を、第３インバータ６（３）によりＷＵ相間交流電圧に同期して制御する。 The phase detection units 12 (1) to 12 (3) detect the phases of the interphase UV, VW, and WV of the three-phase AC power supply 3, respectively, and the current sensors 7 (1) to 7 (3) of the motor 1 respectively. The phase current flowing through each set winding is detected and output to the control unit 8. The control unit 8 controls the current flowing through the three-phase windings 2U (1) to 2W (1) of the first set of the motor 1 by the first inverter 6 (1) in synchronization with the UV-phase AC voltage. The current flowing through the two sets of three-phase windings 2U (2) to 2W (2) is controlled by the second inverter 6 (2) in synchronization with the VW interphase AC voltage, and the third set of three-phase windings 2U ( 3) The current flowing through 2W (3) is controlled by the third inverter 6 (3) in synchronization with the WU interphase AC voltage.

そして、制御部８は、ベクトル制御を行う際に用いるｑ軸電流指令値ＩｑRef＿baseを、速度指令値ωrefとモータ１の速度ωとの差に基づく速度制御の結果に、３相交流電源３の周波数の２倍値に関連した演算パラメータであるｓｉｎ２θｕｖを乗じて生成する。これにより、各組巻線のトルクＴｍ１〜Ｔｍ３に生じている脈動を相殺して、比較的簡単な構成でモータ１を低振動・低騒音で駆動することができる。 Then, the control unit 8 uses the q-axis current command value IqRef_base used when performing vector control as the result of speed control based on the difference between the speed command value ωref and the speed ω of the motor 1, and the frequency of the three-phase AC power supply 3. It is generated by multiplying sin 2 θuv, which is an arithmetic parameter related to the double value of. As a result, the pulsation generated in the torques Tm1 to Tm3 of each set winding can be canceled out, and the motor 1 can be driven with low vibration and low noise with a relatively simple configuration.

（第２実施形態）
以下、第１実施形態と同一部分には同一符号を付して説明を省略し、異なる部分について説明する。図１５に示すように、第２実施形態では、第１実施形態の制御部８を、各インバータ６（１），６（２），６（３）に対応させて３つに分割した第１制御部２１（１），第２制御部２１（２），第３制御部２１（３）を用いる。各制御部２１（１），２１（２），２１（３）は互いに通信を行う通信部を備えている。 (Second Embodiment)
Hereinafter, the same parts as those in the first embodiment are designated by the same reference numerals, description thereof will be omitted, and different parts will be described. As shown in FIG. 15, in the second embodiment, the control unit 8 of the first embodiment is divided into three parts corresponding to the inverters 6 (1), 6 (2), and 6 (3). The control unit 21 (1), the second control unit 21 (2), and the third control unit 21 (3) are used. Each control unit 21 (1), 21 (2), 21 (3) includes a communication unit that communicates with each other.

例えば、共通の処理であるモータ１の速度制御を制御部２１（１）が行い、その結果であるｑ軸電流指令値ＩqRef＿baseを制御部２１（２），２１（３）に送信する。制御部２１（２），２１（３）は、受信したｑ軸電流指令値ＩqRef＿baseに基づき各々の電流制御部１５（２）及び変調制御部１６（２），電流制御部１５（３）及び変調制御部１６（３）で演算を行い、対応するインバータ６（２），６（３）にスイッチング信号を出力する。 For example, the control unit 21 (1) performs speed control of the motor 1, which is a common process, and transmits the result q-axis current command value IqRef_base to the control units 21 (2) and 21 (3). The control units 21 (2) and 21 (3) are the current control unit 15 (2), the modulation control unit 16 (2), the current control unit 15 (3), and the modulation based on the received q-axis current command value IqRef_base. The control unit 16 (3) performs an operation, and outputs a switching signal to the corresponding inverters 6 (2) and 6 (3).

以上のように第２実施形態によれば、モータ１の第１組の３相巻線２Ｕ（１）〜２Ｗ（１）に流れる電流を制御する第１制御部２１（１）と、第２組の３相巻線２Ｕ（２）〜２Ｗ（２）に流れる電流を制御する第２制御部２１（２）と、第３組の３相巻線２Ｕ（３）〜２Ｗ（３）に流れる電流を制御する第３制御部２１（３）とを備える。これらの制御部２１（１）〜２１（３）は互いに通信可能に構成され、各制御部２１（１）〜２１（３）がベクトル制御を行う際に用いるｑ軸電流指令値ＩqRef＿baseは、第１制御部２１（１）における速度制御の結果に基づいて生成する。 As described above, according to the second embodiment, the first control unit 21 (1) that controls the current flowing through the three-phase windings 2U (1) to 2W (1) of the first set of the motor 1 and the second control unit 21 (1). It flows through the second control unit 21 (2) that controls the current flowing through the three-phase windings 2U (2) to 2W (2) of the set and the three-phase windings 2U (3) to 2W (3) of the third set. It includes a third control unit 21 (3) that controls the current. These control units 21 (1) to 21 (3) are configured to be able to communicate with each other, and the q-axis current command value IqRef_base used when each control unit 21 (1) to 21 (3) performs vector control is the first. 1 Generated based on the result of speed control in the control unit 21 (1).

各制御部２１（１），２１（２），２１（３）は、一般的な単一の３相モータを駆動できる数のポート数を持った、小ピン数のマイコンなどの演算器を用いて実現することができるため、安価な構成でモータ制御装置を実現できる。 Each control unit 21 (1), 21 (2), 21 (3) uses an arithmetic unit such as a microcomputer having a small number of pins and having a number of ports capable of driving a general single three-phase motor. Therefore, the motor control device can be realized with an inexpensive configuration.

（第３実施形態）
図１６は、本実施形態のモータ駆動システムを適用した空気調和機３０の構成を示す。ヒートポンプシステム３１を構成する圧縮機３２は、圧縮部３３とモータ１を同一の鉄製密閉容器３５内に収容して構成され、モータ１のロータシャフトが圧縮部３３に連結されている。モータ１は、第１又は第２実施形態の駆動装置により駆動される。そして、圧縮機３２、四方弁３６、室内側熱交換器３７、減圧装置３８、室外側熱交換器３９は、熱伝達媒体流路たるパイプにより閉ループを構成するように接続されている。尚、圧縮機３２は、例えばロータリ型の圧縮機である。空気調和機３０は、上記のヒートポンプシステム３１を有して構成されている。 (Third Embodiment)
FIG. 16 shows the configuration of the air conditioner 30 to which the motor drive system of the present embodiment is applied. The compressor 32 constituting the heat pump system 31 is configured by accommodating the compression unit 33 and the motor 1 in the same iron closed container 35, and the rotor shaft of the motor 1 is connected to the compression unit 33. The motor 1 is driven by the drive device of the first or second embodiment. The compressor 32, the four-way valve 36, the indoor heat exchanger 37, the decompression device 38, and the outdoor heat exchanger 39 are connected so as to form a closed loop by a pipe serving as a heat transfer medium flow path. The compressor 32 is, for example, a rotary type compressor. The air conditioner 30 includes the above-mentioned heat pump system 31.

暖房時には、四方弁３６は実線で示す状態にあり、圧縮機３２の圧縮部３３で圧縮された高温冷媒は、四方弁３６から室内側熱交換器３７に供給されて凝縮し、その後、減圧装置３８で減圧され、低温となって室外側熱交換器３９に流れ、ここで蒸発して圧縮機３２へと戻る。一方、冷房時には、四方弁３６は破線で示す状態に切り替えられる。このため、圧縮機３２の圧縮部３３で圧縮された高温冷媒は、四方弁６から室外側熱交換器３９に供給されて凝縮し、その後、減圧装置３８で減圧され、低温となって室内側熱交換器３７に流れ、ここで蒸発して圧縮機３２へと戻る。そして、室内側、室外側の各熱交換器３７，３９には、それぞれファン４０，４１により送風が行われ、その送風によって各熱交換器３７，３９と室内空気、室外空気の熱交換が効率良く行われるように構成されている。 At the time of heating, the four-way valve 36 is in the state shown by the solid line, and the high-temperature refrigerant compressed by the compressor 33 of the compressor 32 is supplied from the four-way valve 36 to the indoor heat exchanger 37 to condense, and then the decompression device. The pressure is reduced at 38, the temperature becomes low, and the heat flows to the outdoor heat exchanger 39, where it evaporates and returns to the compressor 32. On the other hand, during cooling, the four-way valve 36 is switched to the state shown by the broken line. Therefore, the high-temperature refrigerant compressed by the compressor 33 of the compressor 32 is supplied from the four-way valve 6 to the outdoor heat exchanger 39 to be condensed, and then depressurized by the decompression device 38 to become a low temperature on the indoor side. It flows through the heat exchanger 37, where it evaporates and returns to the compressor 32. Fans 40 and 41 blow air to the indoor and outdoor heat exchangers 37 and 39, respectively, and the heat exchange between the heat exchangers 37 and 39 and the indoor air and outdoor air is efficient. It is configured to be done well.

このように、本実施形態の３組巻線モータ１を駆動するシステムを空気調和機３０に適用することで、空調運転を低振動・低騒音で行うことができる。 As described above, by applying the system for driving the three sets of winding motors 1 of the present embodiment to the air conditioner 30, the air conditioning operation can be performed with low vibration and low noise.

（その他の実施形態）
第１〜第３位相検出部は、３相交流電源の電流・直流電圧からそれぞれの位相を推定する構成でも良い。
本発明のいくつかの実施形態を説明したが、これらの実施形態は例として提示したものであり、発明の範囲を限定することは意図していない。これら新規な実施形態は、その他の様々な形態で実施されることが可能であり、発明の要旨を逸脱しない範囲で種々の省略、置き換え、変更を行うことができる。これらの実施形態やその変形は、発明の範囲や要旨に含まれると共に、特許請求の範囲に記載された発明とその均等の範囲に含まれる。 (Other embodiments)
The first to third phase detectors may be configured to estimate their respective phases from the current and DC voltage of the three-phase AC power supply.
Although some embodiments of the present invention have been described, these embodiments are presented as examples and are not intended to limit the scope of the invention. These novel embodiments can be implemented in various other embodiments, and various omissions, replacements, and changes can be made without departing from the gist of the invention. These embodiments and modifications thereof are included in the scope and gist of the invention, and are also included in the scope of the invention described in the claims and the equivalent scope thereof.

図面中、１は３組巻線構造モータ、２Ｕ〜２Ｗは３相巻線、４（１）〜４（３）は第１〜第３整流回路、６（１）〜６（３）は第１〜第３インバータ、７（１）〜７（３）は電流センサ、８は制御部、９（１）〜９（３）は電圧センサ、１０は位置センサ、１１は速度制御部、１２は位相検出部、２１（１）〜２１（３）は第１〜第３制御部、３０は空気調和機を示す。 In the drawing, 1 is a 3-set winding structure motor, 2U to 2W are 3-phase windings, 4 (1) to 4 (3) are first to third rectifier circuits, and 6 (1) to 6 (3) are first. 1st to 3rd inverters, 7 (1) to 7 (3) are current sensors, 8 are control units, 9 (1) to 9 (3) are voltage sensors, 10 are position sensors, 11 are speed control units, and 12 are. The phase detection unit, 21 (1) to 21 (3) indicate the first to third control units, and 30 indicates an air conditioner.

Claims (3)

それぞれが独立した３組の３相巻線を備え、９個の巻線端子を有する３組巻線構造モータを駆動対象とするもので、
３相交流電源の第１相と第２相との間の第１相間交流電圧，第２相と第３相との間の第２相間交流電圧，第３相と第１相との間の第３相間交流電圧を、それぞれ直流に変換する第１〜第３交流直流変換回路と、
前記第１交流直流変換回路の正側端子及び負側端子と、前記モータの第１組の３相巻線端子との間に接続される第１インバータと、
前記第２交流直流変換回路の正側端子及び負側端子と、前記モータの第２組の３相巻線端子との間に接続される第２インバータと、
前記第３交流直流変換回路の正側端子及び負側端子と、前記モータの第３組の３相巻線端子との間に接続される第３インバータと、
３相交流電源の３相の位相又は３相間の位相を検出する第１〜第３位相検出部と、
前記モータの第１組〜第３組の３相巻線端子にそれぞれ流れる電流を検出する第１〜第３電流検出部と、
前記モータのロータ回転位置を検出する位置検出部と、
前記モータの第１組の３相巻線に流れる電流を、前記第１インバータにより前記第１相間交流電圧に同期して制御し、
前記モータの第２組の３相巻線に流れる電流を、前記第２インバータにより前記第２相間交流電圧に同期して制御し、
前記モータの第３組の３相巻線に流れる電流を、前記第３インバータにより前記第３相間交流電圧に同期して制御する制御部とを備え、
前記制御部は、前記ロータ回転位置及び前記第１〜第３電流検出部により検出された電流に基づいてベクトル制御を行う際に用いるｑ軸電流指令値を、速度指令値と前記モータの速度との差に基づく速度制御の結果に、前記交流電源の周波数の２倍値に関連した演算パラメータを乗じて生成する３組巻線構造モータの駆動装置。 It is intended to drive a three-set winding structure motor, each of which has three independent sets of three-phase windings and has nine winding terminals.
The first-phase AC voltage between the first and second phases of a three-phase AC power supply, the second-phase AC voltage between the second and third phases, and the third-phase and first-phase The 1st to 3rd AC / DC conversion circuits that convert the 3rd phase AC voltage to DC, respectively.
A first inverter connected between the positive and negative terminals of the first AC / DC conversion circuit and the three-phase winding terminal of the first set of the motor.
A second inverter connected between the positive and negative terminals of the second AC / DC conversion circuit and the second set of three-phase winding terminals of the motor.
A third inverter connected between the positive and negative terminals of the third AC / DC conversion circuit and the third set of three-phase winding terminals of the motor.
The first to third phase detectors that detect the phase of the three phases of a three-phase AC power supply or the phase between the three phases,
The first to third current detection units that detect the current flowing through the three-phase winding terminals of the first to third sets of the motor, respectively.
A position detection unit that detects the rotor rotation position of the motor, and
The current flowing through the first set of three-phase windings of the motor is controlled by the first inverter in synchronization with the first-phase AC voltage.
The current flowing through the second set of three-phase windings of the motor is controlled by the second inverter in synchronization with the second-phase AC voltage.
A control unit that controls the current flowing through the three-phase windings of the third set of the motor in synchronization with the AC voltage between the third phases by the third inverter is provided .
The control unit uses the speed command value and the speed of the motor as the q-axis current command value used when performing vector control based on the rotor rotation position and the current detected by the first to third current detection units. A drive device for a three-set winding structure motor that is generated by multiplying the result of speed control based on the difference between the above and the calculation parameters related to the double value of the frequency of the AC power supply . 前記制御部は、前記モータの第１組の３相巻線に流れる電流を制御する第１制御部と、
前記モータの第２組の３相巻線に流れる電流を制御する第２制御部と、
前記モータの第３組の３相巻線に流れる電流を制御する第３制御部とを備え、
前記第１〜第３制御部は、互いに通信可能に構成され、各制御部がベクトル制御を行う際に用いるｑ軸電流指令値は、何れか１つの制御部における速度制御の結果に基づいて生成される請求項１記載の３組巻線構造モータの駆動装置。 The control unit includes a first control unit that controls a current flowing through a first set of three-phase windings of the motor.
A second control unit that controls the current flowing through the second set of three-phase windings of the motor, and
It is provided with a third control unit that controls the current flowing through the three-phase winding of the third set of the motor.
The first to third control units are configured to communicate with each other, and the q-axis current command value used when each control unit performs vector control is generated based on the result of speed control in any one control unit. 3 Kumimakisen structure motor driving apparatus according to claim 1 Symbol placement is. それぞれが独立した３組の３相巻線を備え、９個の巻線端子を有する３組巻線構造モータと、
このモータを駆動する請求項１又は２記載の３組巻線構造モータの駆動装置と、
前記モータを介して駆動される圧縮機とを備える空気調和機。 A three-set winding structure motor, each with three independent sets of three-phase windings and nine winding terminals.
The drive device for the three-set winding structure motor according to claim 1 or 2, which drives this motor, and
An air conditioner including a compressor driven via the motor.
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