JP6802271B2 - Devices and methods for generating electromagnetic waves on transmission media - Google Patents

Description

Mutual reference of related applications This application is entitled "Apparatus and Methods for Priority Non-Interfering Electromagnetic Waves on an Insulated Conductor" filed by Henry et al. On October 14, 2016. It is a partial continuation application of the specification 929 and claims its priority, and this US patent application is "Apparatus and Methods for Generating Non-Interfering" filed by Henry et al. On October 14, 2016. It is a partial continuation application of the specification of Publication No. 15 / 293,819 of the US patent application named "Electromagnetic Waves on an Unintegrated Controller", which claims its priority, and this US patent application is claimed on October 2016. U.S. Patent Application Publication No. 60, Partial Application No. 29, Partial Application No. 29, Part of the U.S. Patent Application No. 29, Priority 29, Priority, Priority, Priority, Priority This US patent application is filed by Henry et al. On September 23, 2016, and is the US patent application publication No. 15 entitled "Apparatus and Methods for Sending or Receiving Electromagnetic Signals". / 274,987 This is a partial continuation application of the specification, claiming its priority, and this US patent application was filed by Henry et al. On December 10, 2015, "Method and Apparatus for Coupling". It is a partial continuation application of the specification of Publication No. 14 / 965, 523 of the US patent application named "an Antonio to a Device" and claims its priority. This US patent application was filed in October 2015. "Method and Apparatus for Coupling an Antonio to a" filed by Adriazola et al. On the 16th. It is a partial continuation application of U.S. Patent Application Publication No. 14 / 885,463 named "Device" and claims its priority. All sections of the above application are incorporated herein by reference in their entirety. All sections of US Patent Application Publication No. 14 / 799,272, entitled "Apparatus and Methods for Transmitting Willless Signals," filed by Henry et al. On July 14, 2015, are hereby by reference. It is used as a whole.

The present disclosure relates to devices and methods for generating electromagnetic waves on a transmission medium.

As smartphones and other portable devices become more prevalent and data usage increases, macrocell base station devices and existing wireless infrastructures require higher bandwidth capacity than ever before to meet increasing demand. There is. Small cell deployments are being driven to provide additional mobile bandwidth, in which microcells and picocells provide coverage for much smaller areas than previous macrocells.

In addition, most homes and businesses are growing and relying on broadband data access for services such as voice, video, and Internet browsing. Broadband access networks include satellite, 4G or 5G wireless, power line communication, fiber, cable, and telephone network.

Here, an attached drawing that is not necessarily drawn to a certain scale is referred to.

It is a block diagram which shows the non-limiting embodiment of an example of a waveguide communication system by various aspects described herein. FIG. 3 is a block diagram illustrating a non-limiting embodiment of an example of a transmitting device according to the various aspects described herein. FIG. 6 is a graphic diagram illustrating a non-limiting embodiment of an example of an electromagnetic field distribution according to the various aspects described herein. FIG. 6 is a graphic diagram illustrating a non-limiting embodiment of an example of an electromagnetic field distribution according to the various aspects described herein. FIG. 5 is a graphic diagram illustrating a non-limiting embodiment of an example of frequency response according to the various aspects described herein. FIG. 5 is a graphic diagram illustrating a non-limiting embodiment of an example of a longitudinal cross section of an insulated wire showing a field of waveguided electromagnetic waves at different operating frequencies according to the various aspects described herein. It is a graphic diagram which shows the non-limiting embodiment of the example of the electromagnetic field distribution by the various aspects described herein. It is a block diagram which shows the non-limiting embodiment of the example of the arc coupling by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of the example of the arc coupling by various aspects described herein. FIG. 6 is a block diagram showing a non-limiting embodiment of an example of a stub coupler according to the various aspects described herein. It is a figure which shows the non-limiting embodiment of the example of the electromagnetic distribution by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a coupler and a transmitter / receiver by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a coupler and a transmitter / receiver by various aspects described herein. FIG. 6 is a block diagram showing a non-limiting embodiment of an example of a double stub coupler according to the various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a repeater system by various aspects described herein. FIG. 6 shows a block diagram showing a non-limiting embodiment of an example of a bidirectional repeater according to the various aspects described herein. FIG. 3 is a block diagram showing a non-limiting embodiment of an example of a waveguide system according to the various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a waveguide communication system by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of the system which manages a power grid communication system by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of the system which manages a power grid communication system by various aspects described herein. FIG. 6 shows a flow chart illustrating a non-limiting embodiment of an example of a method of detecting and mitigating disturbances that occur in the communication networks of the systems of FIGS. 16A and 16B. FIG. 6 shows a flow chart illustrating a non-limiting embodiment of an example of a method of detecting and mitigating disturbances that occur in the communication networks of the systems of FIGS. 16A and 16B. It is a block diagram which shows the non-limiting embodiment of an example of a transmission medium which propagates a wave-guided electromagnetic wave. It is a block diagram which shows the non-limiting embodiment of an example of a transmission medium which propagates a wave-guided electromagnetic wave. It is a block diagram which shows the non-limiting embodiment of an example of a transmission medium which propagates a wave-guided electromagnetic wave. FIG. 5 is a block diagram illustrating a non-limiting embodiment of an example of a cohesive transmission medium according to the various aspects described herein. An example non-limiting embodiment of a plot showing crosstalk between a first transmission medium and a second transmission medium of the cohesive transmission medium of FIG. 18D according to the various aspects described herein. It is a block diagram which shows. FIG. 5 is a block diagram illustrating a non-limiting embodiment of an example of a cohesive transmission medium that reduces crosstalk, according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of the transmission medium which has an internal waveguide by various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of the transmission medium which has an internal waveguide by various aspects described herein. FIG. 8 is a block diagram illustrating a non-limiting embodiment of an example connector configuration that can be used with the transmission medium of FIGS. 18A, 18B, or 18C. FIG. 8 is a block diagram illustrating a non-limiting embodiment of an example connector configuration that can be used with the transmission medium of FIGS. 18A, 18B, or 18C. It is a block diagram which shows the non-limiting embodiment of an example of the transmission medium in which a waveguided electromagnetic wave propagates. FIG. 3 is a block diagram illustrating a non-limiting embodiment of an example of a cohesive transmission medium that reduces crosstalk, according to various aspects described herein. FIG. 5 is a block diagram illustrating a non-limiting embodiment of an example of an exposed stub from a cohesive transmission medium used as an antenna, according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits or receives an electromagnetic wave according to various aspects described herein. FIG. 3 is a block diagram showing a non-limiting embodiment of an example of a dielectric antenna and corresponding gain and field intensity plots according to the various aspects described herein. FIG. 3 is a block diagram showing a non-limiting embodiment of an example of a dielectric antenna and corresponding gain and field intensity plots according to the various aspects described herein. FIG. 6 is a block diagram showing a non-limiting embodiment of an example of a dielectric antenna coupled to a lens and corresponding gain and field intensity plots according to the various aspects described herein. FIG. 6 is a block diagram showing a non-limiting embodiment of an example of a dielectric antenna coupled to a lens and corresponding gain and field intensity plots according to the various aspects described herein. FIG. 6 is a block diagram showing a non-limiting embodiment of an example of a dielectric antenna coupled to a lens having a ridge and corresponding gain and field intensity plots according to the various aspects described herein. FIG. 6 is a block diagram showing a non-limiting embodiment of an example of a dielectric antenna coupled to a lens having a ridge and corresponding gain and field intensity plots according to the various aspects described herein. FIG. 3 is a block diagram illustrating a non-limiting embodiment of an example of a dielectric antenna having an elliptical structure according to various aspects described herein. FIG. 3 is a block diagram illustrating a non-limiting embodiment of an example of a near-field signal and a long-range field signal emitted by the dielectric antenna of FIG. 19G according to various aspects described herein. FIG. 3 is a block diagram of a non-limiting embodiment of an example of a dielectric antenna that tunes a long-range wireless signal according to various aspects described herein. It is a block diagram of one non-limiting embodiment of an example of a flange that can be coupled to a dielectric antenna according to the various aspects described herein. It is a block diagram of one non-limiting embodiment of an example of a flange that can be coupled to a dielectric antenna according to the various aspects described herein. FIG. 3 is a block diagram of a non-limiting embodiment of an example of a flange, waveguide, and dielectric antenna assembly according to the various aspects described herein. FIG. 3 is a block diagram of a non-limiting embodiment of an example of a dielectric antenna coupled to a gimbal that directs a wireless signal generated by the dielectric antenna according to the various aspects described herein. It is a block diagram of one non-limiting embodiment of an example of a dielectric antenna according to various aspects described herein. FIG. 3 is a block diagram of a non-limiting embodiment of an array of dielectric antennas that can be configured to manipulate wireless signals according to the various aspects described herein. FIG. 5 is a side block diagram of a non-limiting embodiment of an example of a cable, flange, and dielectric antenna assembly according to the various aspects described herein. FIG. 5 is a side block diagram of a non-limiting embodiment of an example of a cable, flange, and dielectric antenna assembly according to the various aspects described herein. FIG. 5 is a side block diagram of a non-limiting embodiment of an example of a cable, flange, and dielectric antenna assembly according to the various aspects described herein. FIG. 5 is a side block diagram of a non-limiting embodiment of an example of a cable, flange, and dielectric antenna assembly according to the various aspects described herein. FIG. 5 is a side block diagram of a non-limiting embodiment of an example of a cable, flange, and dielectric antenna assembly according to the various aspects described herein. FIG. 5 is a side block diagram of a non-limiting embodiment of an example of a cable, flange, and dielectric antenna assembly according to the various aspects described herein. FIG. 5 is a side block diagram of a non-limiting embodiment of an example of a cable, flange, and dielectric antenna assembly according to the various aspects described herein. FIG. 5 is a side block diagram of a non-limiting embodiment of an example of a cable, flange, and dielectric antenna assembly according to the various aspects described herein. It is a front block diagram of a non-limiting embodiment of an example of a dielectric antenna according to the various aspects described herein. It is a front block diagram of a non-limiting embodiment of an example of a dielectric antenna according to the various aspects described herein. It is a front block diagram of a non-limiting embodiment of an example of a dielectric antenna according to the various aspects described herein. FIG. 5 is a block diagram showing a non-limiting embodiment of an example transmission medium of FIG. 18A used to guide electromagnetic waves waveguided over a power line supported by a utility pole. FIG. 5 is a block diagram showing a non-limiting embodiment of an example transmission medium of FIG. 18A used to guide electromagnetic waves waveguided over a power line supported by a utility pole. It is a block diagram of one non-limiting embodiment of an example of a communication network according to various aspects described herein. It is a block diagram of one non-limiting embodiment of an example of an antenna mount used in a communication network according to various aspects described herein. It is a block diagram of one non-limiting embodiment of an example of an antenna mount used in a communication network according to various aspects described herein. It is a block diagram of one non-limiting embodiment of an example of an antenna mount used in a communication network according to various aspects described herein. A flow chart of a non-limiting embodiment of an example of a method of transmitting a downlink signal is shown. A flow chart of a non-limiting embodiment of an example of a method of transmitting an uplink signal is shown. A flow chart of a non-limiting embodiment of an example of a method of inducing and receiving an electromagnetic wave on a transmission medium is shown. A flow chart of a non-limiting embodiment of an example of a method of inducing and receiving an electromagnetic wave on a transmission medium is shown. A flow diagram of a non-limiting embodiment of an example of a method of transmitting a wireless signal from a dielectric antenna is shown. A flow diagram of a non-limiting embodiment of an example of a method of receiving a wireless signal in a dielectric antenna is shown. The flow chart of one non-limiting embodiment of the method of detecting and mitigating the disturbance generated in the communication network is shown. FIG. 3 is a block diagram illustrating a non-limiting embodiment of an example of electromagnetic field alignment that reduces propagation loss due to the accumulation of water on a transmission medium, according to various aspects described herein. FIG. 3 is a block diagram illustrating a non-limiting embodiment of an example of electric field intensities of different electromagnetic waves propagating through a cable shown in FIG. 20H, according to various aspects described herein. FIG. 3 is a block diagram illustrating a non-limiting embodiment of an example of electric field intensities of different electromagnetic waves propagating through a cable shown in FIG. 20H, according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of the electric field of a Goubo wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of the electric field of a hybrid wave by various aspects described herein. It is a block diagram which shows one non-limiting embodiment of the electric field characteristic of a hybrid wave vs. a goobo wave according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of the mode size of a hybrid wave at various operating frequencies according to various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits a hybrid wave by various aspects described herein. It is a block diagram which shows one non-limiting embodiment of an example of a waveguide device which transmits a hybrid wave by various aspects described herein. FIG. 3 is a block diagram illustrating a non-limiting embodiment of an example of a hybrid wave transmitted by the waveguide devices of FIGS. 21A and 21B, according to various aspects described herein. A flow chart of a non-limiting embodiment of an example of a method of managing electromagnetic waves is shown. It is a block diagram which shows the non-limiting embodiment of the example of the waveguide device by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of the example of the waveguide device by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of the example of the waveguide device by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of the example of the waveguide device by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of the example of the waveguide device by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. A flow chart of a non-limiting embodiment of an example of a method of managing electromagnetic waves is shown. It is a block diagram which shows the non-limiting embodiment of the example of the substantially orthogonal wave mode by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of the example of the insulating conductor by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a non-insulated conductor according to various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of the oxide layer formed on the non-insulating conductor of FIG. 25AB according to various aspects described herein. FIG. 3 is a block diagram showing a non-limiting embodiment of an example of a spectral plot according to the various aspects described herein. FIG. 3 is a block diagram showing a non-limiting embodiment of an example of a spectral plot according to the various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example of a wave mode and an electric field plot by various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example which transmits the orthogonal wave mode by the method of FIG. 25Y by the various aspects described herein. It is a block diagram which shows the non-limiting embodiment of an example which transmits the orthogonal wave mode by the method of FIG. 25Y by the various aspects described herein. FIG. 5 is a block diagram illustrating an example non-limiting embodiment in which wave modes are selectively received by the method of FIG. 25Y, according to various aspects described herein. FIG. 5 is a block diagram illustrating an example non-limiting embodiment in which wave modes are selectively received by the method of FIG. 25Y, according to various aspects described herein. FIG. 5 is a block diagram illustrating an example non-limiting embodiment in which wave modes are selectively received by the method of FIG. 25Y, according to various aspects described herein. FIG. 5 is a block diagram illustrating an example non-limiting embodiment in which wave modes are selectively received by the method of FIG. 25Y, according to various aspects described herein. It is a block diagram of a non-limiting embodiment of an example of a computational environment according to various aspects described herein. It is a block diagram of a non-limiting embodiment of an example of a mobile network platform according to various aspects described herein. It is a block diagram of a non-limiting embodiment of an example of a communication device according to various aspects described herein.

Here, one or more embodiments are described with reference to the drawings, in which the same reference numerals are used to refer to the same elements throughout. In the following description, a number of details are provided for purposes of illustration to provide a complete understanding of the various embodiments. However, it is clear that various embodiments can be implemented without the use of these details (and without application to any particular networked environment or standard).

In one embodiment, a waveguide communication system is presented that transmits and receives communication signals such as data or other signaling via waveguided electromagnetic waves. Waveguided electromagnetic waves include, for example, surface waves or other electromagnetic waves coupled or waveguided to a transmission medium. It will be appreciated that a variety of transmission media can be used in conjunction with waveguide communication without departing from the exemplary embodiments. Examples of such transmission media can include one or more of the following, alone or in combination of one or more: whether insulated or not, and either single wire or stranded wire. Wires, whether or not; conductors of other shapes or configurations, including wire bundles, cables, rods, rails, pipes; non-conductors such as dielectric pipes, rods, rails or other dielectric members; conductors and dielectrics Combination with material; or other waveguide transmission medium.

The induction of waveguided electromagnetic waves in a transmission medium can be independent of any potential, charge, or current that is injected into or transmitted to the transmission medium as part of an electrical circuit. For example, if the transmission medium is an electric wire, a small current can be formed in the electric wire in response to the propagation of the waveguide along the electric wire, which can be caused by the propagation of the electromagnetic wave along the electric wire surface, and electricity. It should be understood that it is not formed in response to the potential, charge, or current injected into the wire as part of the circuit. Therefore, the traveling electromagnetic wave on the wire does not require a circuit to propagate along the wire surface. Therefore, the wire is a single layer transmission line that is not part of the circuit. Also, in some embodiments, no wires are required and the electromagnetic waves can propagate along a single wire transmission medium that is not a wire.

More generally, the "waved electromagnetic wave" or "waved wave" described herein is at least a portion of the transmission medium (eg, bare wire or other conductor, dielectric, insulated wire, conduit or other. A physical object that is a hollow element, a bundle of insulated wires or other bundles of wires coated, coated, or surrounded by a dielectric or insulator, or another form of solid, or other non-liquid or non-gas transmission medium. It is done by the presence of, at least partially directed or guided by the physical object, and propagates along the transmission path of the physical object. Such physical objects induce the propagation of waved electromagnetic waves at the interface of the transmission medium (eg, the outer surface, the inner surface, the inner surface between the outer and inner surfaces, or other boundaries between the elements of the transmission medium). Propagation of waved electromagnetic waves can carry energy, data, and / or other signals from the transmitting device to the receiving device along the transmission path. Can be done.

Unlike free-space propagation of wireless signals such as unguided (or uncoupled) electromagnetic waves, whose intensity decreases in inverse proportion to the square of the travel distance of the non-guided electromagnetic waves, the wave-guided electromagnetic waves are more than those received by the non-guided electromagnetic waves. It can propagate along the transmission medium with a magnitude loss per unit distance.

The electrical circuit allows the electrical signal to propagate from the transmitting device to the receiving device via an electrical route and an electrical feedback path, respectively. These electrical routes and electrical return paths can be carried out via two conductors, such as two wires or one wire and a common ground that functions as a second conductor. In particular, the current (direct current and / or alternating current) from the transmitting device flows through the electrical route and returns to the source via the electrical feedback path as a reverse current. More specifically, the electron flow in one conductor flowing away from the transmitting device returns to the receiving device in the opposite direction via the second conductor or ground. Unlike electrical signals, the waved electromagnetic waves are transmitted media (eg, non-conductive materials such as bare conductors, insulating conductors, conduits, dielectric strips, or any other type of object suitable for surface wave propagation). From the transmitting device to the receiving device along, or vice versa, the transmission medium does not have to be part of an electrical circuit between the transmitting device and the receiving device (ie, the transmitting device and the receiving device). It can propagate (without the need for an electrical feedback path). Electromagnetic waves can propagate in open circuits, i.e. circuits that do not have an electrical feedback path or circuits that have breaks or gaps that block the flow of current through the circuit, but the electromagnetic waves are actually part of the electrical circuit. It should be noted that it can also propagate along the surface of the transmission medium. That is, the electromagnetic wave can travel along the first surface of the transmission medium having the electrical route and / or along the second surface of the transmission medium having the electrical feedback path. Thus, the waveguided electromagnetic waves can propagate from the transmitting device to the receiving device and vice versa along the surface of the transmission medium with or without an electrical circuit.

This allows, for example, the transmission of waveguided electromagnetic waves along a transmission medium (eg, a dielectric strip) that does not have a conductive component. Thereby, for example, a wave-guided electromagnetic wave propagating along a transmission medium having only one conductor (eg, an electromagnetic wave propagating along the surface of one bare conductor or along the surface of one insulating conductor). Alternatively, it is possible to transmit electromagnetic waves (electromagnetic waves) propagating in the insulator of the insulating conductor in whole or in part. The transmission medium comprises one or more conductive components, and the wave-guided electromagnetic waves propagating along the transmission medium sometimes flow within the one or more conductive components in the direction of the wave-guided electromagnetic waves. Even when generating current, such wave-guided electromagnetic waves travel from the transmitting device to the receiving side along the transmission medium without the reverse current flow on the electrical return path from the receiving device back to the transmitting device. Can be propagated to the device. Therefore, such wave-guided electromagnetic wave propagation can be referred to as propagation through a single transmission line or propagation through a surface wave transmission line.

In a non-limiting example, consider a coaxial cable having a central conductor and a ground shield separated by an insulator. Normally, in the electrical system, the first terminal of the transmitting (and receiving) device can be connected to the center conductor, and the second terminal of the transmitting (and receiving) device is connected to the ground shield. be able to. When the transmitting device injects an electrical signal into the center conductor through the first terminal, the electrical signal propagates along the center conductor, sometimes producing a forward current and corresponding electron flow in the center conductor. At the same time, the feedback current and the reverse flow of electrons are generated in the ground shield. The same situation applies to 2-terminal receiving devices.

In contrast, different embodiments of transmission media (including coaxial cables) for the transmission and reception of electromagnetic waves guided without electrical circuits (ie, without electrical routes or electrical feedback paths, depending on the viewpoint). Consider a wave-guided wave communication system as described in the present disclosure, which can utilize. In one embodiment, for example, the wave-guided wave communication system of the present disclosure is such that it induces a wave-guided electromagnetic wave propagating along the outer surface of the coaxial cable (eg, the outer cover or insulating layer of the coaxial cable). Can be configured. Waveguided electromagnetic waves generate a forward current on the ground shield, while the waveguided electromagnetic waves are within the central conductor to allow the waveguided electromagnetic waves to propagate along the outer surface of the coaxial cable. Does not require feedback current. In other words, the wave-guided electromagnetic wave produces a forward current on the ground shield, but the wave-guided electromagnetic wave does not generate a reverse feedback current in the center conductor (or other electrical feedback path). The same is true for other transmission media used by wave-guided wave communication systems for the transmission and reception of wave-guided electromagnetic waves.

For example, a waveguided electromagnetic wave guided by a wave-guided wave communication system on the outer surface of a bare or insulated conductor does not generate a reverse feedback current in the electrical feedback path and is the outer surface of the bare conductor. Alternatively, it can propagate along the other surface of the insulating conductor. Another difference is that when most of the signal energy in an electrical circuit is guided by the flow of electrons in the conductor itself, it is waveguided over the outer surface of the bare conductor in the wave-guided wave communication system. The forward current generated by an electromagnetic wave in a bare conductor is minimal, and most of the signal energy of the electromagnetic wave is concentrated above the outer surface of the bare conductor rather than inside the bare conductor. Further, the waveguided electromagnetic waves coupled to the outer surface of the insulating conductor generate minimal forward current in one or more central conductors of the insulating conductor, and most of the signal energy of the electromagnetic waves is inside the insulator and in the insulator. / Or concentrate in the area above the outer surface of the insulating conductor-in other words, most of the signal energy of the electromagnetic wave is concentrated outside the central conductor of the insulating conductor.

Therefore, electrical systems that require two or more conductors to carry forward and reverse currents in separate conductors to allow propagation of the electrical signal injected by the transmitting device are at the interface of the transmission medium. It differs from a waveguide system that guides a wave-guided electromagnetic wave over the interface of a transmission medium, which does not require an electrical circuit to allow the wave-guided electromagnetic wave to propagate along.

The waved electromagnetic waves described in the present disclosure are to be coupled to or waveguideed by a transmission medium and are longer than a small distance on or along the outer surface of the transmission medium ( It should be further noted that in order to propagate non-trivial distations), it may have an electromagnetic field structure that resides primarily or substantially outside the transmission medium. In other embodiments, the electromagnetic wave to be waveguide is a transmission medium in order to be coupled to or waveguideed by the transmission medium and to propagate a distance longer than a small distance within the transmission medium. It can have an electromagnetic field structure that resides primarily or substantially inside. In other embodiments, the waved electromagnetic waves are transmitted in order to be coupled to or waved through the transmission medium and to propagate along the transmission medium over a distance greater than a small distance. It can have an electromagnetic field structure that is partially inside and partly outside the medium. The desired electric field structure in one embodiment has a variety of factors including the desired transmission distance, the characteristics of the transmission medium itself, and the environmental conditions / characteristics outside the transmission medium (eg, the presence of rainfall, fog, atmospheric conditions, etc.). Can vary based on.

The various embodiments described herein are "waveguide coupled devices", "guides" that transmit and / or extract waveguided electromagnetic waves to and / or from transmission media at millimeter wave frequencies (eg, 30 GHz to 300 GHz). In connection with a coupling device, which can be more simply referred to as a "waveguide coupler", or more simply a "coupler", "coupler", or "transmitter", where the millimeter wavelength is the outer circumference of the wire or other cross-sectional dimension Etc., which are small compared to one or more dimensions of the coupling device and / or transmission medium, or can be low frequency microwaves such as 300 MHz to 30 GHz. Transmission is a strip of dielectric material, arc, or other length; horn, monopole, rod, slot, or other antenna; array of antennas; magnetic resonance cavity, or other resonant coupler; coil, stripline, It can be generated to propagate as a wave guided by a waveguide or a coupling device such as another coupling device. In operation, the coupling device receives electromagnetic waves from a transmitter or transmission medium. The electromagnetic field structure of an electromagnetic wave can exist inside the coupling device, outside the coupling device, or any combination thereof. When the coupled device is close to the transmission medium, at least a portion of the electromagnetic wave is coupled to the transmission medium and continues to propagate as a waveguided electromagnetic wave. In the round trip, the coupling device can extract the waveguide from the transmission medium and transfer these electromagnetic waves to the receiver.

According to an exemplary embodiment, the surface wave is a transmission medium, such as an outer or outer surface of the wire or another surface of the wire adjacent to or exposed to another type of medium with different properties (eg, dielectric constant). It is a type of waveguide that is guided by the surface of. In fact, in an exemplary embodiment, the surface of the wire that guides the surface wave can represent a transition surface between two different types of media. For example, in the case of a bare wire or non-insulated wire, the surface of the wire can be the outside or outer conductor surface of the bare wire or non-insulated wire exposed to air or free space. As another example, in the case of an insulated wire, the surface of the wire may further be one or more waveguides, depending on the relative differences in the properties (eg, dielectric constant) of the insulator, air, and / or conductor. Depending on the frequency and propagation mode, it can be the conductive part of the wire that comes into contact with the insulator part of the wire, or it can be the other surface of the wire that is exposed to the air or free space, or otherwise of the wire. It can be any material area between the surface of the insulator and the conductive portion of the wire that contacts the insulator portion of the wire.

According to an exemplary embodiment, the term "periphery" of a wire or other transmission medium used in conjunction with a waveguide refers to a circular or substantially circular field distribution, a symmetric electromagnetic field distribution (eg, an electric field). , Magnetic fields, electromagnetic fields, etc.), or basic waveguide propagation modes, such as waveguides, which have at least partially other basic mode patterns around the wire or other transmission medium. In addition, when propagating "around" an electric wire or other transmission medium, the waveguide is not only in the fundamental wave propagation mode (eg, zero-order mode), but also in addition or instead, in a higher-order waveguide mode (eg, for example). , Primary mode, secondary mode, etc.), asymmetric mode, and / or waveguide propagation mode including non-basic wave propagation modes such as other waveguides (surface waves) having a non-circular field distribution around the wire or transmission medium. You can do so according to. As used herein, the term "waveguide mode" refers to a waveguide propagation mode of a transmission medium, coupled device, or other system component of a waveguide communication system.

For example, such a non-amphitheater distribution is characterized by one or more azimuth lobes characterized by relatively high field intensities, and / or by relatively low field intensities, zero field intensities or substantial zero field intensities. It can be unilateral or multidirectional with one or more nulls or null regions characterized. Further, the field distribution, according to an exemplary embodiment, is such that one or more regions of the azimuthal orientation are higher than one or more other regions of orientation (or magnetic field strength thereof). It can also be varied as a function of longitudinal orientation around the wire to have a combination). It will be appreciated that the relative orientation or position of the waveguide in higher or asymmetric mode can change as the waveguide travels along the wire.

As used herein, the term "millimeter wave" can refer to an electromagnetic wave / signal within the "millimeter wave frequency band" of 30 GHz to 300 GHz. The term "microwave" can refer to electromagnetic waves / signals within the "microwave frequency band" of 300 MHz to 300 GHz. The term "radio frequency" or "RF" can refer to electromagnetic waves / signals within the "radio frequency band" of 10 kHz to 1 THz. The wireless signals, electrical signals, and waveguided electromagnetic waves described herein are in any desired frequency range, such as within, above, or below the millimeter and / or microwave frequency band. It is understood that it can be configured to work in. In particular, when the coupling device or transmission medium contains a conductive element, the frequency of the waveguided electromagnetic waves carried by the coupling device and / or propagated along the transmission medium is less than the average collision frequency of the electrons in the conductive element. possible. Further, the frequency of the waveguided electromagnetic wave carried by the coupling device and / or propagated along the transmission medium can be a non-optical frequency, eg, a radio frequency below the optical frequency range starting at 1 THz.

As used herein, the term "antenna" can refer to a transmitting system or device that is part of a transmitting or receiving system that transmits / radiates or receives wireless signals.

According to one or more embodiments, the method is to receive a plurality of communication signals and, by the transmitting device, to generate a plurality of electromagnetic waves, at least partially coupled to an isolated transmission medium, according to the plurality of communication signals. By generating an inducing wireless signal, the plurality of electromagnetic waves propagates along an insulated transmission medium without an electrical feedback path, and each electromagnetic wave of the plurality of electromagnetic waves transmits at least one communication signal of the plurality of communication signals. A generation of transmitted electromagnetic waves having a signal multiplexing configuration that reduces interference between the plurality of electromagnetic waves and allows the receiving device to extract at least one communication signal from each of the plurality of electromagnetic waves. Including to do.

According to one or more embodiments, the transmitter can include a generator and a circuit coupled to the generator. The controller receives a plurality of communication signals and, according to the plurality of communication signals, generates a signal for inducing a plurality of electromagnetic waves coupled to a dielectric layer of a transmission medium at least partially. Each electromagnetic wave transmits at least one communication signal of a plurality of communication signals, and the plurality of electromagnetic waves perform operations including generating, having a signal multiplexing configuration that reduces interference between the plurality of electromagnetic waves. ..

According to one or more embodiments, the device generates a means of receiving the plurality of communication signals and, according to the plurality of communication signals, generates a signal that induces a plurality of electromagnetic waves bound to the dielectric material at least partially. Each electromagnetic wave of a plurality of electromagnetic waves transmits at least one communication signal of a plurality of communication signals, and the plurality of electromagnetic waves have a multiplexing configuration for reducing interference between the plurality of electromagnetic waves. including.

Here, with reference to FIG. 1, a block diagram 100 showing a non-limiting embodiment of an example of a waveguide communication system is shown. In operation, the transmitting device 101 receives one or more communication signals 110 containing data from a communication network or other communication device, generates a waveguide 120, and transmits the data via the transmission medium 125 to the transmitting device 102. Communicate to. The transmitting device 102 receives the waveguide 120 and converts it into a communication signal 112 containing data to be transmitted to a communication network or other communication device. Multiplexing by frequency division multiplexing, time division multiplexing, code division multiplexing, multiplexing by different wave propagation modes, etc. by modulation techniques such as phase modulation, frequency modulation, orthogonal amplitude modulation, amplitude modulation, multicarrier modulation such as orthogonal frequency division multiplexing, etc. The waveguide 120 can be modulated to carry data by the access technique of, and by other modulation and access methods.

One or more communication networks may be wireless communications such as mobile data networks, cellular voice data networks, wireless local area networks (eg, WiFi or 802.xx networks), satellite communications networks, personal area networks, or other wireless networks. Can include networks. One or more communication networks include a telephone network, an Ethernet network, a local area network, a wide area network such as the Internet, a broadband access network, a cable network, an optical fiber network, or a wired communication network such as another wired network. You can also. Communication devices include network edge devices, bridge devices or home gateways, set-top boxes, broadband modems, telephone adapters, access points, base stations, or other fixed communication devices, in-vehicle gateways or auto-mobile computers, laptop computers, tablets, It can include mobile communication devices such as smartphones, mobile phones, or other communication devices.

In an exemplary embodiment, the waveguide communication system 100 can operate in a bidirectional manner, in which the transmitting device 102 communicates from a communication network or device, including other data. The signal 112 is received, the waveguide 122 is generated, and the other data described above is conveyed to the transmission device 101 via the transmission medium 125. In this mode of operation, the transmitting device 101 receives the waveguide 122 and converts it into a communication signal 110 containing the above other data to be transmitted to the communication network or device. Multiplexing by frequency division multiplexing, time division multiplexing, code division multiplexing, multiplexing by different wave propagation modes, etc. by modulation techniques such as phase modulation, frequency modulation, orthogonal amplitude modulation, amplitude modulation, multicarrier modulation such as orthogonal frequency division multiplexing, etc. The waveguide 122 can be modulated to carry data by this access technique, as well as by other modulation and access methods.

The transmission medium 125 can include a cable having at least one interior surrounded by a dielectric material such as an insulator or other dielectric cover, coating, or other dielectric material, the dielectric material corresponding to the outer surface. It has a peripheral edge. In an exemplary embodiment, the transmission medium 125 operates as a single layer transmission line to guide the transmission of electromagnetic waves. The transmission medium 125 may include an electric wire when implemented as a single wire transmission system. The wires may or may not be insulated, and may be single wires or stranded wires (eg, braided). In other embodiments, the transmission medium 125 may include conductors of other shapes or configurations, including wire bundles, cables, rods, rails, pipes. In addition, the transmission medium 125 includes non-conductors such as dielectric pipes, rods, rails or other dielectric members, combinations of conductors and dielectric materials, conductors without dielectric material, or other waveguide transmission media. be able to. It should be noted that the transmission medium 125 may otherwise include any of the transmission media described above.

Further, as mentioned above, the waveguides 120 and 122 can be contrasted with the conventional propagation of power or signals through wireless transmission over free space / air or through conductors of wires via electrical circuits. In addition to the propagation of the waveguides 120 and 122, the transmission medium 125 optionally propagates power or other communication signals in a conventional manner as part of one or more electrical circuits. Can include electric wires.

Here, with reference to FIG. 2, a block diagram 200 showing a non-limiting embodiment of an example of a transmitting device is shown. The transmitting device 101 or 102 includes a communication interface (I / F) 205, a transmitter / receiver 210, and a coupler 220.

In one example of operation, the communication interface 205 receives a communication signal 110 or 112 containing data. In various embodiments, the communication interface 205 is an LTE or other cellular voice data protocol, WiFi or 802.11 protocol, WIMAX protocol, ultra-broadband protocol, Bluetooth protocol, Zigbee protocol, direct broadcast satellite (DBS) or other satellite. It can include a wireless interface that receives wireless communication signals according to a communication protocol, or a wireless standard protocol such as another wireless protocol. In addition or instead, the communication interface 205 is an Ethernet protocol, a universal serial bus (USB) protocol, a cable data service interface standard (DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire (IEEE1394) protocol, or Includes a wired interface that operates according to other wired protocols. In addition to standards-based protocols, the communication interface 205 can work with other wired or wireless protocols. Further, the communication interface 205 can optionally operate with a protocol stack that includes a plurality of protocol layers including a MAC protocol, a transport protocol, an application protocol, and the like.

In one example of operation, the transmitter / receiver 210 generates an electromagnetic wave based on a communication signal 110 or 112 that carries data. The electromagnetic wave has at least one carrier frequency and at least one corresponding wavelength. The carrier frequency is as low as 300 MHz to 30 GHz within the millimeter wave frequency band of 30 GHz to 300 GHz such as the carrier frequency within the range of 60 GHz or 30 GHz to 40 GHz or within the microwave frequency range of 26 GHz to 30 GHz, 11 GHz, 6 GHz, or 3 GHz. Although it can be in the frequency band, it will be appreciated that in other embodiments, other carrier frequencies are possible. In one operating mode, the transmitter / receiver 210 communicates one or more communication signals in order to transmit an electromagnetic signal in the microwave band or millimeter wave band as a waveguiding electromagnetic wave waveguide or coupled by a transmission medium 125. Simply upconvert 110 or 112. In another mode of operation, the communication interface 205 converts the communication signal 110 or 112 into a baseband signal or a signal near the baseband, or extracts data from the communication signal 110 or 112 and the transmitter / receiver 210 transmits. Therefore, the data, baseband signal or signal near the baseband is modulated into a high frequency carrier. Data communication of one or more of the communication signals 110 or 112 by the transmitter / receiver 210 modulating the data received via the communication signal 110 or 112 and by encapsulation into a payload of a different protocol or by a simple frequency shift. Please understand that the protocol can be stored. Alternatively, the transmitter / receiver 210 may convert the data received via the communication signal 110 or 112 into another protocol that is different from one or more data communication protocols of the communication signal 110 or 112.

In one example of operation, the coupler 220 couples the electromagnetic wave to the transmission medium 125 as a waveguided electromagnetic wave that carries one or more communication signals 110 or 112. Although the above description has focused on the operation of the transmitter / receiver 210 as a transmitter, the transmitter / receiver 210 receives electromagnetic waves that carry other data from a single-line transmission medium via a coupler 220, and the other data described above. It can also operate to generate a communication signal 110 or 112 via a communication interface 205 containing data. Consider an embodiment in which an additional waveguided electromagnetic wave carries other data propagating along the transmission medium 125 as well. The combiner 220 can also couple this additional electromagnetic wave from the transmission medium 125 to the transmitter / receiver 210 for reception.

The transmitting device 101 or 102 includes an optional training controller 230. In an exemplary embodiment, the training controller 230 is implemented by a stand-alone processor or a processor shared with one or more other components of the transmitting device 101 or 102. The training controller 230 is based on feedback data received by the transmitter / receiver 210 from at least one remote transmitting device coupled to receive the waveguided electromagnetic wave, the carrier frequency of the waveguided electromagnetic wave, the modulation scheme, And / or select the waveguide mode.

In an exemplary embodiment, the waveguided electromagnetic wave transmitted by the remote transmission device 101 or 102 also carries data propagating along the transmission medium 125. The data from the remote transmitting device 101 or 102 can be generated to include feedback data. In operation, the coupler 220 also couples the electromagnetic waves waveguided from the transmission medium 125, and the transmitter / receiver receives the electromagnetic waves, processes the electromagnetic waves, and extracts feedback data.

In an exemplary embodiment, the training controller 230 operates on the basis of feedback data to evaluate multiple frequency candidates, modulation scheme candidates, and / or transmission mode candidates to enhance performance such as throughput, signal strength, and the like. , Select the carrier frequency, modulation method, and / or transmission mode to reduce propagation loss, etc.

Consider the following example. The transmitting device 101 transmits a plurality of waveguides as a test signal such as a pilot wave or another test signal with a corresponding plurality of frequency candidates and / or mode candidates directed to the remote transmitting device 102 coupled to the transmission medium 125. By transmitting, the operation is started under the control of the training controller 230. In addition or instead, the waveguide can contain test data. The test data may indicate specific frequency candidates and / or waveguide mode candidates for the signal. In one embodiment, the training controller 230 in the remote transmit device 102 receives test signals and / or test data from any waveguide appropriately received, with the best frequency candidate and / or waveguide mode candidate, a set of tolerances. Determine the ranked order of possible frequency candidates and / or waveguide mode candidates, or frequency candidates and / or waveguide mode candidates. This selection of frequency candidates and / and waveguide mode candidates is made by the training controller 230 based on one or more optimization criteria such as received signal strength, bit error rate, packet error rate, signal-to-noise ratio, propagation loss, etc. Will be generated. The training controller 230 generates feedback data indicating the selected frequency candidate and / and the waveguide mode candidate, and transmits the feedback data to the transmitter / receiver 210 for transmission to the transmission device 101. The transmitting devices 101 and 102 can then communicate data with each other based on the selected frequency candidate and / or waveguide mode.

In other embodiments, the waveguided electromagnetic waves containing the test signals and / or test data are transmitted by the remote transmitting device 102 for reception and analysis by the training controller 230 of the transmitting device 101 that initiated these waves. Reflected, relayed, or otherwise looped back to 101. For example, the transmitting device 101 can send a signal to the remote transmitting device 102 to start the test mode, in which the physical reflectors are switched on the line and the termination impedance causes reflections. The loopback mode is switched on to recouple the electromagnetic wave to the source transmitting device 102 and / or the repeater mode is enabled to amplify the electromagnetic wave and retransmit it to the source transmitting device 102. The training controller 230 in the source transmitting device 102 receives test signals and / or test data from any waveguide appropriately received and determines selected frequency candidates and / or waveguide mode candidates.

Although the above procedure has been described in a startup or initialization mode of operation, each transmitting device 101 or 102 may similarly transmit a test signal, a frequency candidate or waveguide via a non-test such as normal transmission. Mode candidates may be evaluated, or frequency candidates or waveguide mode candidates may be evaluated at other times or continuously. In an exemplary embodiment, the communication protocol between the transmitting devices 101 and 102 is in a required or periodic test mode in which a complete test or a more limited test of a subset of frequency and waveguide mode candidates is tested and evaluated. Can be included. In other modes of operation, performance degradation due to disturbances, weather conditions, etc. can trigger reentry into such test modes. In an exemplary embodiment, the receiver bandwidth of the transmitter / receiver 210 is wide enough or swept to receive all frequency candidates, or by the training controller 230, the receiver bandwidth of the transmitter / receiver 210 is all. Can be selectively adjusted to a training mode that is wide enough to receive frequency candidates or swept.

Here, with reference to FIG. 3, a graphic diagram 300 showing an example of a non-limiting embodiment of an electromagnetic field distribution is shown. In this embodiment, the transmission medium 125 in the air includes an inner conductor 301 and an insulating jacket 302 of a dielectric material, as shown in cross section. FIG. 300 includes different grayscales representing different electromagnetic field intensities generated by waveguide propagation with asymmetric and non-basic waveguide modes.

In particular, the electromagnetic field distribution corresponds to a modal "sweet spot" that enhances the propagation of waveguided electromagnetic waves along an insulated transmission medium and reduces end-to-end transmission loss. In this particular mode, the electromagnetic wave is guided by the transmission medium 125 and propagates along the outer surface of the transmission medium-in this case the outer surface of the insulating jacket 302. Electromagnetic waves are partially embedded in the insulator and partially radiated on the outer surface of the insulator. In this way, the electromagnetic waves are "lightly" coupled to the insulator, allowing long-range electromagnetic wave propagation with low propagation loss.

As shown, the waveguide has a field structure that is primarily or substantially outside the transmission medium 125 that functions to guide the electromagnetic waves. The area inside the conductor 301 has no field or is negligible, if any. Similarly, the region inside the insulating jacket 302 also has low field strength. Most of the electromagnetic field strength is distributed in the lobe 304 and its vicinity on the outer surface of the insulating jacket 302. The presence of the asymmetric waveguide mode is indicated by the high electromagnetic field strength at the top and bottom (in the orientation of the figure) of the outer surface of the insulation jacket 302-what is the very small field strength on the other side of the insulation jacket 302? In contrast.

The example shown corresponds to a 38 GHz electromagnetic wave guided by a wire having a diameter of 1.1 cm and a dielectric insulation thickness of 0.36 cm. Since the electromagnetic waves are guided by the transmission medium 125 and most of the field strength is concentrated in the air outside the insulating jacket 302 within a limited distance on the outer surface, the waveguide is a transmission medium with very low loss. 125 can propagate downward in the longitudinal direction. In the example shown, this "limited distance" corresponds to a distance from the outer surface that is less than half the maximum cross-sectional dimension of the transmission medium 125. In this case, the maximum cross-sectional dimension of the wire corresponds to an overall diameter of 1.82 cm, but this value can vary with the size and shape of the transmission medium 125. For example, if the transmission medium 125 has a rectangular shape with a height of 0.3 cm and a width of 0.4 cm, the maximum cross-sectional dimension is 0.5 cm diagonally and the corresponding limited distance is 0.25 cm. is there. The size of the area containing most of the field strength also changes with frequency and generally increases with decrease in carrier frequency.

It should also be noted that the components of the waveguide communication system, such as couplers and transmission media, may have their own cutoff frequency in each waveguide mode. The cutoff frequency generally refers to the lowest frequency designed for a particular waveguide mode to be supported by that particular component. In an exemplary embodiment, the particular asymmetric propagation mode shown is on the transmission medium 125 by electromagnetic waves having frequencies within a limited range (Fc-2Fc, etc.) of the low cutoff frequency Fc of this particular asymmetric mode. Is guided to. The low cutoff frequency Fc is unique to the characteristics of the transmission medium 125. In the case of the indicated embodiment comprising an inner conductor 301 surrounded by an insulating jacket 302, this cutoff frequency may vary based on the dimensions and characteristics of the insulating jacket 302 and potentially the dimensions and characteristics of the inner conductor 301. It can be determined experimentally to have the desired mode pattern. However, it should be noted that similar effects can be found with hollow dielectrics or insulators without internal conductors. In this case, the cutoff frequency can vary based on the dimensions and properties of the hollow dielectric or insulator.

At frequencies lower than the low cutoff frequency, it is difficult to induce the asymmetric mode to the transmission medium 125, all propagation fails, and only a small distance propagates. As the frequency increases beyond the limited frequency range before and after the cutoff frequency, the asymmetric mode shifts more and more inward of the insulation jacket 302. At frequencies much higher than the cutoff frequency, the field strength is no longer concentrated outside the insulation jacket, but primarily inside the insulation jacket 302. The transmission medium 125 provides a strong waveguide for electromagnetic waves and propagation is still possible, but the range is more limited by the increased loss due to propagation within the insulating jacket 302-as opposed to ambient air. is there.

Here, with reference to FIG. 4, a graphic diagram 400 showing an example of a non-limiting embodiment of an electromagnetic field distribution is shown. In particular, a cross-sectional view 400 similar to FIG. 3 is shown using a common reference code used to refer to similar elements. The example shown corresponds to a 60 GHz wave guided by an electric wire having a diameter of 1.1 cm and a dielectric insulation thickness of 0.36 cm. Since the frequency of the waveguide exceeds the limited range of the cutoff frequency of this particular asymmetric mode, much of the field strength is shifted inside the insulating jacket 302. In particular, the field strength is mainly concentrated inside the insulating jacket 302. The transmission medium 125 provides a strong waveguide for the electromagnetic waves and is still capable of propagation, but due to the increased loss due to propagation within the insulating jacket 302, the range is greater when compared to the embodiment of FIG. Be restricted.

Here, with reference to FIG. 5A, a graphic diagram showing a non-limiting embodiment of an example of frequency response is shown. In particular, FIG. 500 presents a graph of end-to-end loss (in dB) as a function of frequency, with electromagnetic field distributions 510, 520, and 530 superimposed at three points on a 200 cm insulated medium voltage wire. The boundary between the insulator and the ambient air is represented by reference numeral 525 in each electromagnetic field distribution.

As discussed in connection with FIG. 3, an example of the desired asymmetric mode of propagation shown is within a limited range of low cutoff frequency Fc of the transmission medium in this particular asymmetric mode (Fc-2Fc, etc.). It is guided to the transmission medium 125 by an electromagnetic wave having a certain frequency. In particular, the electromagnetic field distribution 520 at 6 GHz is within this modal "sweet spot" that enhances electromagnetic wave propagation along the insulated transmission medium and reduces end-to-end transmission losses. In this particular mode, the waveguide is partially embedded in the insulator and partially radiated on the outer surface of the insulator. In this way, the electromagnetic waves are "lightly" coupled to the insulator, allowing long-range guided electromagnetic wave propagation with low propagation loss.

At the low frequencies represented by the electromagnetic field distribution 510 at 3 GHz, the asymmetric mode radiates more strongly, resulting in higher propagation loss. At high frequencies represented by the electromagnetic field distribution 530 at 9 GHz, the asymmetric mode shifts more and more inward of the insulating jacket, providing too much absorption, again resulting in high propagation loss.

Here, referring to FIG. 5B, FIG. 550 is a graphic diagram 550 showing a non-limiting embodiment of an example of a longitudinal cross section of a transmission medium 125 such as an insulated wire showing a field of waveguided electromagnetic waves at various operating frequencies. It is shown. As shown in FIG. 556, when in the cut-off frequency of electromagnetic waves guided corresponds to approximately modal "sweet spot" (f _c), an electromagnetic wave is guided it is loosely bound with the insulated wire, thereby, the absorption Is reduced and the waveguided electromagnetic field is coupled sufficiently to reduce the amount radiated into the environment (eg, air). The low absorption and emission of the wave-guided electromagnetic wave field results in low propagation loss, allowing the wave-guided electromagnetic wave to propagate over longer distances.

As shown in FIG. 554, the operating frequency of the waveguide wave is greater than about twice the cutoff frequency (f _c) - or mentioned manner beyond the scope of the "sweet spot" - the case of increased propagation loss Will increase. More of the field strength of electromagnetic waves occurs inside the insulating layer, increasing propagation loss. In a much higher frequency than the cutoff frequency (f _c), an electromagnetic wave is guided, as shown in FIG. 552, as a result of place emitted by the electromagnetic wave is guided is concentrated on the insulating layer of the wire , Strongly coupled to insulated wires. This further increases the propagation loss due to the absorption of the waveguided electromagnetic waves by the insulating layer. Similarly, as shown in FIG. 558, the propagation loss is increased if much lower than guided by electromagnetic waves of the operating frequency is a cutoff frequency (f _c). In a much lower frequency than the cutoff frequency (f _c), an electromagnetic wave is guided is (or nominally) vulnerable to insulated wire bonded, whereby the environment (e.g., air) have a tendency to radiate in This increases propagation loss due to the radiation of the waveguided electromagnetic waves.

Here, with reference to FIG. 6, a graphic diagram 600 showing an example of a non-limiting embodiment of an electromagnetic field distribution is shown. In this embodiment, the transmission medium 602 is a bare wire as shown in cross section. FIG. 300 includes different grayscales representing different electromagnetic field intensities resulting from the propagation of a waveguide having symmetric and basic waveguide modes at a single carrier frequency.

In this particular mode, the electromagnetic wave is guided by the transmission medium 602 and propagates along the outer surface of the transmission medium-in this case the outer surface of the bare wire. Electromagnetic waves are "lightly" coupled to wires, allowing long-distance electromagnetic wave propagation with low propagation loss. As shown, the waveguide has a field structure that is substantially external to the transmission medium 602 that functions to guide the electromagnetic waves. The area inside the conductor 602 is fieldless or, if any, very small.

Here, with reference to FIG. 7, a block diagram 700 showing a non-limiting embodiment of an example arc coupler is shown. In particular, the combined device is presented for use in a transmitting device such as the transmitting device 101 or 102 presented in connection with FIG. The coupling device includes a transmitter circuit 712 and an arc coupling 704 coupled to a termination or damper 714. The arc coupler 704 can be made of a dielectric material, other low loss insulator (eg, Teflon, polyethylene, etc.), a conductive (eg, metal, non-metal, etc.) material, or any combination of the above materials. As shown, the arc coupler 704 operates as a waveguide and has a wave 706 propagating as a waveguide around the surface of the waveguide of the arc coupler 704. In the embodiments shown, at least a portion of the arc coupler 704 is placed near wire 702 or other transmission medium (such as transmission medium 125) to deliver waveguide 708 over the wire. Coupling between the arc coupler 704 and wire 702 or other transmission medium can be facilitated as described in the document. The arc coupler 704 can be arranged such that a portion of the curved arc coupler 704 is tangentially, parallel or substantially parallel to the wire 702. The portion of the arc coupler 704 parallel to the wire can be any point where the apex of the curve or the tangent of the curve is parallel to the wire 702. When the arc coupler 704 is positioned or arranged in this way, the wave 706 traveling along the arc coupler 704 is at least partially coupled to the wire 702 and as a waveguide 708 around or around the wire surface of the wire 702. It propagates in the longitudinal direction along the electric wire 702. The waveguide 708 can be characterized as a surface wave or other electromagnetic wave that is guided or coupled by wire 702 or other transmission medium.

The portion of the wave 706 that is not coupled to the wire 702 propagates along the arc coupler 704 as a wave 710. It will be appreciated that the arc coupler 704 can be configured and placed at various locations in relation to the wire 702 to achieve the desired level of coupling or non-coupling of the wave 706 to the wire 702. For example, the curvature and / or length of an arc coupler 704 that is parallel or substantially parallel and its separation distance to wire 702 (which, in one embodiment, may include zero separation distance) is an exemplary embodiment. It can change without departing from its form. Similarly, the arrangement of the arc coupler 704 in relation to the wire 702 is the unique characteristics of the wire 702 and the arc coupler 704 (eg, thickness, composition, electromagnetic properties, etc.) and the characteristics of the waves 706 and 708 (eg, eg). , Frequency, energy level, etc.) can be changed.

The waveguide 708 remains parallel or substantially parallel to the wire 702 even when the wire 702 bends and bends. The curvature of wire 702 can increase transmission loss, which also depends on the diameter, frequency, and material of the wire. When the dimensions of the arc coupler 704 are selected for efficient transmission, most of the power in the wave 706 is transferred to the wire 702 and very little power remains in the wave 710. While traveling along a path parallel or substantially parallel to wire 702, the nature of the waveguide 708 is still multimodal, including having a mode that is non-basic or asymmetric with or without a basic transmission mode. It will be understood that it can be (discussed herein). In one embodiment, non-basic or asymmetric modes can be utilized to minimize transmission loss and / or obtain increased propagation distance.

Note that the term parallel is generally a geometric configuration that is often not strictly achievable in real-world systems. Therefore, the term parallel as used in the present disclosure refers to an approximation rather than an exact configuration when used in the description of embodiments disclosed in the present disclosure. In one embodiment, substantially parallel can include an approximation that is within 30 degrees of true parallel in all dimensions.

In one embodiment, the wave 706 may exhibit one or more wave propagation modes. The arc coupler mode may depend on the shape and / or design of the coupler 704. The wave 706 in one or more arc coupler modes can generate, influence, or influence the waveguide 708 in one or more wave propagation modes propagating along the wire 702. However, it should be noted that the waveguide mode present in the waveguide 706 may be the same as or different from the waveguide mode of the waveguide 708. In this way, the waveguide 706 in one or more waveguide modes may not move to the waveguide 708, and the waveguide 708 in one or more waveguide modes is transferred to the waveguide 706. It is possible that it did not exist. It should also be noted that the cutoff frequency of the arc coupler 704 in a particular waveguide mode may differ from the cutoff frequency of wire 702 or the cutoff frequency of other transmission media in the same mode. For example, wire 702 or other transmission medium can operate slightly above the cutoff frequency of a particular waveguide mode, while the arc coupler 704 has a cutoff frequency of the same mode due to its low loss. It can operate well above, for example, to induce larger couplings and transmissions, and can operate just below the cutoff frequency of the same mode, or related to the cutoff frequency of the arc coupler in that mode. And can work in some other way.

In one embodiment, the wave propagation mode on the wire 702 can be similar to the arc coupler mode, because the waves 706 and 708 both propagate around the outside of the arc coupler 704 and the wire 702, respectively. To do. In some embodiments, when the wave 706 is coupled to wire 702, the mode can change form, or create or generate a new mode, due to the coupling between the arc coupler 704 and wire 702. can do. For example, differences in size, material, and / or impedance of the arc coupler 704 and wire 702 may create additional modes that do not exist in the arc coupler mode and / or suppress some of the arc coupler modes. Can be done. The wave propagation mode is a basic transverse electromagnetic mode (pseudo TEM _{00) in which} only a small electric and / or magnetic field extends in the propagation direction, and the electric and magnetic fields extend radially outward while the waveguide propagates along the wire. ) Can be included. This waveguide mode can be donut-shaped with a minority of the electromagnetic fields present in the arc coupler 704 or wire 702.

Waves 706 and 708 can include basic TEM modes in which the field extends radially outward, as well as other non-basic (eg, asymmetric, higher order, etc.) modes. Specific wave propagation modes have been described above, but are based on the frequencies used, the design of the arc coupler 704, the dimensions and composition of the wire 702 and its surface properties, its insulator, if any, the electromagnetic properties of the surrounding environment, etc. Therefore, other wave propagation modes such as transverse electrical (TE) and transverse magnetic (TM) modes are also possible. Depending on the frequency, the electrical and physical properties of the wire 702, and the particular wave propagation mode generated, the waveguide 708 is along the conductive surface of the non-oxidized, non-oxidized, non-insulated wire, insulated wire. Note that and / or can proceed along the insulating surface of the insulated wire.

In one embodiment, the diameter of the arc coupler 704 is smaller than the diameter of the wire 702. At the millimeter band wavelengths used, the arc coupler 704 supports a single waveguide mode that makes up the wave 706. This single waveguide mode can change when coupled to wire 702 as waveguide 708. If the arc coupler 704 is larger, it can support more than one waveguide mode, but these additional waveguide modes may not efficiently couple to wire 702, resulting in coupling. Losses can be high. However, in some alternative embodiments, for example, when higher coupling loss is desired or when used in conjunction with other techniques to reduce coupling loss (eg, impedance matching with tapering, etc.). The diameter of the arc coupler 704 can be greater than or equal to the diameter of the wire 702.

In one embodiment, the wavelengths of the waves 706 and 708 are equal to or smaller than the outer circumference of the arc coupler 704 and wire 702. In one example, when the wire 702 has a diameter of 0.5 cm and a corresponding outer circumference of about 1.5 cm, the transmission wavelength is about 1.5 cm or less and corresponds to frequencies of 70 GHz or higher. In another embodiment, suitable frequencies for transmit and carrier signals are in the range of 30 GHz to 100 GHz, perhaps from about 30 GHz to 60 GHz, in one example about 38 GHz. In one embodiment, if the outer circumferences of the arc coupler 704 and wire 702 are equal to or greater in size than the wavelength of transmission, the waves 706 and 708 are to support the various communication systems described herein. It may exhibit multiple wave propagation modes, including basic and / or non-basic (symmetric and / or asymmetric) modes that propagate over a sufficient distance. Thus, the waves 706 and 708 can include two or more types of electric and magnetic field configurations. In one embodiment, as the waveguide 708 propagates down wire 702, the electric and magnetic field configurations remain the same from end to end of wire 702. In other embodiments, when the waveguide 708 faces interference (distortion or obstruction) or loses energy due to transmission loss or scattering, the magnetic and electric field configurations are such that the waveguide 708 propagates down wire 702. It can change as you do.

In one embodiment, the arc coupler 704 can be made of nylon, Teflon, polyethylene, polyamide, or other plastic. In other embodiments, other dielectric materials are possible. The wire surface of the wire 702 can be a metal with a bare metal surface, or can be insulated with a plastic, dielectric, insulator, or other coating, jacket, or sheath. In one embodiment, the dielectric or other non-conductive / insulated waveguide can be paired with a bare / metal wire or an insulated wire. In other embodiments, the metal and / or conductive waveguide can be paired with bare / metal or insulated wire. In one embodiment, the oxide layer on the bare metal surface of wire 702 (eg, resulting from exposure of the bare metal surface to oxygen / air) is also an insulation similar to that provided by some insulator or sheath. Properties or dielectric properties can be provided.

It is noted that the graphic representations of the waves 706, 708, and 710 are presented solely to show the principle that the waves 706 guide or otherwise transmit the waveguide 708 to wire 702, which operates, for example, as a single layer transmission line. I want to. Wave 710 represents the portion of wave 706 that remains in the arc coupler 704 after the generation of the waveguide 708. The actual electric and magnetic fields generated as a result of such wave propagation are the frequencies utilized, one or more specific wave propagation modes, the design of the arc coupler 704, the dimensions and composition of the wire 702, and the surface. It can be changed according to the characteristics, optional insulation, electromagnetic characteristics of the surrounding environment, and the like.

Note that the arc coupler 704 may include a termination circuit or damper 714 at the end of the arc coupler 704 capable of absorbing residual radiation or energy from the wave 710. The termination circuit or damper 714 can avoid and / or minimize residual radiation or energy from the wave 710 reflected towards the transmitter circuit 712. In one embodiment, the termination circuit or damper 714 may include other components that perform termination resistance and / or impedance matching to attenuate reflections. In some embodiments, it may not be necessary to use a termination circuit or damper 714 if the coupling efficiency is high enough and / or the wave 710 is small enough. For simplicity, these transmitters 712 and termination circuits or dampers 714 may not be shown in other figures, but in their embodiments, perhaps transmitters and termination circuits or dampers may be used. it can.

Further, a single arc coupler 704 that produces a single waveguide 708 is presented, but multiple arc couplers 704 arranged at different points along the wire 702 and / or in different directions around the wire. Can be used to generate and receive multiple waveguides 708 in the same or different frequencies, the same or different phases, and the same or different wave propagation modes.

FIG. 8 shows block diagram 800 showing a non-limiting embodiment of an example arc coupler. In the embodiments shown, at least one portion of the coupler 704 is placed close to wire 702 or other transmission medium (such as transmission medium 125) and the arc coupler 704 and wire 702 or other transmission medium. A portion of the waveguide 806 can be extracted as the waveguide 808 as described herein by facilitating the coupling between them. The arc coupler 704 can be arranged such that a portion of the curved arc coupler 704 is tangentially, parallel or substantially parallel to the wire 702. The portion of the arc coupler 704 parallel to the wire can be any point where the apex of the curve or the tangent of the curve is parallel to the wire 702. When the arc coupler 704 is positioned or arranged in this way, the wave 806 traveling along the wire 702 is at least partially coupled to the arc coupler 704 and received along the arc coupler 704 as a waveguide 808. Propagate to the side device (not explicitly shown). The portion of the wave 806 that is not coupled to the arc coupler propagates as a wave 810 along the wire 702 or other transmission medium.

In one embodiment, the wave 806 may exhibit one or more wave propagation modes. The arc coupler mode may depend on the shape and / or design of the coupler 704. One or more modes of waveguide 806 can generate, influence, or influence one or more waveguide modes of waveguide 808 propagating along the arc coupling 704. However, it should be noted that the waveguide mode present in the waveguide 806 may be the same as or different from the waveguide mode of the waveguide 808. In this way, the waveguide 806 in one or more waveguide modes may not move to the waveguide 808, and the waveguide 808 in one or more waveguide modes is transferred to the waveguide 806. It is possible that it did not exist.

Here, with reference to FIG. 9A, block diagram 900 showing a non-limiting embodiment of an example of a stub coupler is shown. In particular, the coupling device including the stub coupling device 904 is presented for use in a transmission device such as the transmission device 101 or 102 presented in connection with FIG. The stub coupler 904 can be made of a dielectric material, other low loss insulator (eg, Teflon, polyethylene, etc.), a conductive (eg, metal, non-metal, etc.) material, or any combination of the above materials. As shown, the stub coupler 904 operates as a waveguide and has a wave 906 propagating as a waveguide around the surface of the waveguide of the stub coupler 904. In the embodiments shown, at least one portion of the stub coupler 904 is placed near wire 702 or other transmission medium (such as transmission medium 125) and the stub coupler 904 is as described herein. It can facilitate coupling between the wire and the wire 702 or other transmission medium and send the waveguide 908 to the wire.

In one embodiment, the stub coupler 904 is curved and the end of the stub coupler 904 can be connected to, fixed to, or mechanically coupled to the wire 702. When the end of the stub coupler 904 is fixed to the wire 702, the end of the stub coupler 904 is parallel or substantially parallel to the wire 702. Alternatively, another portion of the dielectric waveguide beyond the end can be fixed or coupled to wire 702 such that the portion to be fixed or coupled is parallel or substantially parallel to wire 702. The fixture 910 can be another type of non-conductive / dielectric material that is separate from the nylon cable cord or stub coupler 904 or constructed as an integral component of the stub coupler 904. The stub coupler 904 can be adjacent to the wire 702 without surrounding the wire 702.

When the stub coupler 904 is arranged with its ends parallel to the wire 702, as in the arc coupler 704 described in connection with FIG. 7, the waveguide 906 traveling along the stub coupler 904 , It is coupled to the electric wire 702 and propagates as a waveguide 908 around the electric wire surface of the electric wire 702. In an exemplary embodiment, the waveguide 908 can be characterized as a surface wave or other electromagnetic wave.

It should be noted that the graphic representations of the waves 906 and 908 are presented solely to show the principle that the waves 906 guide or otherwise transmit the waveguide 908 to wire 702, which operates, for example, as a single line transmission line. The actual electric and magnetic fields generated as a result of such wave propagation are the shape and / or design of the coupler, the relative position of the dielectric waveguide with respect to the wire, the frequency used, the design of the stub coupler 904, wire 702. It can be changed according to one or more of the dimensions and composition of the electric wire, its surface characteristics, optional insulation of the electric wire 702, electromagnetic characteristics of the surrounding environment, and the like.

In one embodiment, the end of the stub coupler 904 has a tapered shape towards the wire 702 to increase coupling efficiency. In fact, the tapered end of the stub coupler 904 can provide impedance matching to wire 702 and reduce reflections, according to the exemplary embodiments of the present disclosure. For example, the ends of the stub coupler 904 can be taper off to obtain the desired level of coupling between the waves 906 and 908 as shown in FIG. 9A.

In one embodiment, the fixture 910 can be arranged such that there is a short length stub coupler 904 between the fixture 910 and the end of the stub coupler 904. Maximum coupling efficiency is achieved in this embodiment when the length of the end of the stub coupler 904 beyond the fixture 910 is at least several times the wavelength of the frequency being transmitted, regardless of the frequency being transmitted. To.

Here, with reference to FIG. 9B, FIG. 950 is shown showing a non-limiting embodiment of an example of electromagnetic distribution according to the various aspects described herein. In particular, in one example, the electromagnetic distribution in the case of a transmitting device including a coupler 952 shown within a stub coupler constructed of a dielectric material is presented in two dimensions. The coupler 952 couples electromagnetic waves to propagate as a waveguide along the outer surface of the wire 702 or other transmission medium.

Coupler 952 is guided through the electromagnetic wave at the junction of the x ₀ through symmetrical guided mode. Although some of the energy of the electromagnetic waves propagating along the coupler 952 is outside the coupler 952, most of the energy of this electromagnetic wave is contained within the coupler 952. joint portions in the x ₀ is coupled to the wire 702, or other transmission medium electromagnetic waves in the azimuth angle corresponding to the lower portion of the transmission medium. This coupling induces an electromagnetic wave that is guided so as to propagate along the outer surface of the wire 702 or other transmission medium via at least one waveguide mode in direction 956. Most of the energy of the waveguided electromagnetic waves is on or near the outer surface of the wire 702 or other transmission medium. In the example shown, joint portions in the x _0, the surface of the symmetric mode and the wire 702, or other transmission medium through the close proximity to, at least one asymmetric surface modes such as primary mode presented in connection with FIG. 3 It forms an electromagnetic wave that propagates through both.

Note that the graphical representation of the waveguide is presented solely to show examples of waveguide coupling and propagation. The actual electric and magnetic fields generated as a result of such wave propagation are the frequencies utilized, the design and / or configuration of the coupler 952, the dimensions and composition of the wire 702 or other transmission medium, and its surface properties. If it exists, it can be changed according to the insulation, the electromagnetic characteristics of the surrounding environment, and the like.

Here, with reference to FIG. 10A, is shown a block diagram 1000 of a non-limiting embodiment of an example of a combiner and transmitter / receiver system according to the various aspects described herein. The system is an example of a transmitting device 101 or 102. In particular, the communication interface 1008 is an example of the communication interface 205, the stub coupler 1002 is an example of the coupler 220, the transmitter / receiver device 1006, the diplexer 1016, the power amplifier 1014, the low noise amplifier 1018, and the frequency mixer. The 1010 and 1020, and the local oscillator 1012 collectively form an example of the transmitter / receiver 210.

In operation, the transmitter / receiver device 1006 sends and receives waves (eg, waveguide 1004 to stub coupler 1002). The waveguide 1004 can be used by communication interface 1008 to send signals received and transmitted from a host device, base station, mobile device, building, or other device. The communication interface 1008 may be an integral part of the system 1000. Alternatively, the communication interface 1008 can be connected to the system 1000. The communication interface 1008 is a host that utilizes any of a variety of wireless signaling protocols (eg, LTE, WiFi, WiMAX, IEEE802.xx, etc.), including infrared protocols such as the Infrared Data Association (IrDA) protocol or other line-of-sight optical protocols. It can include wireless interfaces that interface with devices, base stations, mobile devices, buildings, or other devices. The communication interface 1008 is a wired interface such as an optical fiber line, a coaxial cable, a twisted pair wire, a category 5 (CAT-5) cable, an Ethernet protocol, a universal serial bus (USB) protocol, and a data service interface standard (DOCSIS) protocol by cable. Communicate with host devices, base stations, mobile devices, buildings, or other devices via protocols such as Digital Subscriber Line (DSL) protocol, Firewire (IEEE1394) protocol, or other wired or optical protocols. It can also include a suitable wired or optical medium. In embodiments where the system 1000 functions as a repeater, the communication interface 1008 may not be needed.

The output signal (eg, Tx) of the communication interface 1008 can be combined with a carrier wave (eg, millimeter wave carrier) generated by the local oscillator 1012 in the frequency mixer 1010. The frequency mixer 1010 can frequency shift the output signal from the communication interface 1008 using a heterodyne technique or other frequency shifting technique. For example, the signals transmitted to and from the communication interface 1008 are long-term evolution (LTE) wireless protocols or other wireless 3G, 4G, 5G or higher-order voice and data protocols, Zigbee, WIMAX, ultra-wideband. Alternatively, the IEEE 802.11 wireless protocol; an Ethernet protocol, a universal serial bus (USB) protocol, a cable data service interface standard (DOCSIS) protocol, a digital subscriber line (DSL) protocol, a wired protocol such as a Firewire (IEEE1394) protocol, or It can be a modulated signal, such as an Orthogonal Frequency Division Multiplexing (OFDM) signal, formatted according to other wired or wireless protocols. In an exemplary embodiment, this frequency conversion can be done in the analog domain and, as a result, the frequency shift can be done regardless of the type of communication protocol used by the base station, mobile device, or in-building device. .. As new communication technologies are developed, the communication interface 1008 can be upgraded (eg, updated with software, firmware, and / or hardware) or replaced, leaving the frequency shift and transmission equipment intact. You can easily upgrade. The carrier wave can then be transmitted to the power amplifier (“PA”) 1014 and can be transmitted via the diplexer 1016 and through the transmitter / receiver device 1006.

The signal received from the transmitter / receiver device 1006 and directed to the communication interface 1008 can be separated from other signals via the diplexer 1016. The received signal can then be transmitted to a low noise amplifier (“LNA”) 1018 for amplification. The frequency mixer 1020 can shift the received signal (in some embodiments, in the millimeter wave band or about 38 GHz) downward to its original frequency with the assistance of the local oscillator 1012. Next, the communication interface 1008 can receive the transmission at the input port (Rx).

In one embodiment, the transmitter / receiver device 1006 is a cylindrical or non-cylindrical metal (eg, it may be hollow in one embodiment, but is not necessarily drawn to scale), or other conductivity. Alternatively, a non-conductive waveguide can be included, with the end of the stub coupler 1002 located within the waveguide or transmitter / receiver device 1006 or in close proximity to the waveguide or transmitter / receiver device 1006. So that when the transmitter / receiver device 1006 produces a transmission, the waveguide couples to the stub coupler 1002 and propagates around the waveguide surface of the stub coupler 1002 as the waveguide 1004. can do. In some embodiments, the waveguide 1004 can propagate partially on the outer surface of the stub coupler 1002 and partially inside the stub coupler 1002. In other embodiments, the waveguide 1004 can propagate substantially or completely over the outer surface of the stub coupler 1002. In yet another embodiment, the waveguide 1004 can propagate substantially or completely inside the stub coupler 1002. In this latter embodiment, the waveguide 1004 radiates at the end of the stub coupler 1002 (such as the tapered end shown in FIG. 4) in order to couple to a transmission medium such as the wire 702 of FIG. Can be done. Similarly, when the waveguide 1004 is arriving (coupled from wire 702 to the stub coupler 1002), the waveguide 1004 enters the transmitter / receiver device 1006 into a cylindrical or conductive waveguide. Join. The transmitter / receiver device 1006 is shown to include a separate waveguide, but utilizes an antenna, cavity resonator, klystron, magnetron, traveling wave tube or other radiation element with or without a separate waveguide. The waveguide can be induced on the coupler 1002.

In one embodiment, the stub coupler 1002 can be composed entirely of a dielectric material (or another suitable insulating material) without the use of any metal or other conductive material. The stub coupler 1002 is nylon, Teflon, polyethylene, polyamide, other plastic, or non-conductive, and is suitable for facilitating the transmission of electromagnetic waves at least on the outer surface of such materials. It can be composed of the following materials. In another embodiment, the stub coupler 1002 may include a core made of conductive / metal and have an outer dielectric surface. Similarly, the transmission medium coupled to the stub coupler 1002 to propagate the electromagnetic waves induced by the stub coupler 1002 or to supply the electromagnetic waves to the stub coupler 1002 is a bare wire or an insulated wire. In addition, it can be composed entirely of dielectric material (or another suitable insulating material) without the use of any metal or other conductive material.

FIG. 10A shows that the opening of the transmitter-receiver device 1006 is much wider than the stub coupler 1002, but this does not follow a certain scale, and in other embodiments the width of the stub coupler 1002 Note that it is as small as or slightly smaller than the opening of the hollow waveguide. Also, although not shown, in one embodiment, the end of the coupler 1002 inserted into the transmitter / receiver device 1006 is tapered to reduce reflections and increase coupling efficiency.

One or more waveguide modes of the waveguide generated by the transmitter / receiver device 1006 before coupling to the stub coupling 1002 are coupled to the stub coupling 1002 and one or more of the waveguide 1004. Wave propagation mode can be derived. The wave propagation mode of the waveguide 1004 may differ from the hollow metal waveguide mode due to the difference in characteristics between the hollow metal waveguide and the dielectric waveguide. For example, the wave propagation mode of the waveguide 1004 can include a basic transverse electromagnetic mode (pseudo TEM ₀₀ ), in which a slight electric field and / or while the waveguide propagates along the stub coupler 1002. Only the magnetic field extends in the propagation direction, and the electric and magnetic fields extend radially outward from the stub coupler 1002. Basic Transverse Electromagnetic Mode The wave propagation mode may or may not exist inside a hollow waveguide. Therefore, the hollow metal waveguide mode used by the transmitter / receiver device 1006 is a waveguide mode that can be effectively and efficiently coupled to the wave propagation mode of the stub coupler 1002.

It will be appreciated that other configurations or combinations of transmitter / receiver device 1006 and stub coupler 1002 are possible. For example, as shown by reference numeral 1000'in FIG. 10B, the stub coupler 1002'is the outer surface of a hollow metal waveguide of transmitter / receiver device 1006' (corresponding circuitry not shown). It can be arranged tangentially or parallel to (with or without gaps). In another embodiment not indicated by reference numeral 1000', the stub coupler 1002'can be placed inside the hollow metal waveguide of the transmitter / receiver device 1006' and the stub coupler 1002'. It is not necessary to align the axis of the transmitter / receiver device 1006'coaxially with the axis of the hollow metal waveguide. In any of these embodiments, the waveguide generated by the transmitter / receiver device 1006'is coupled to the surface of the stub coupler 1002' in basic mode (eg, symmetric mode) and / or non-basic. Waveguide 1004'in one or more wave propagation modes, including modes (eg, asymmetric modes), can be guided onto the stub coupler 1002'.

In one embodiment, the waveguide 1004'can propagate partially on the outer surface of the stub coupler 1002'and partially inside the stub coupler 1002'. In another embodiment, the waveguide 1004'can propagate substantially or completely over the outer surface of the stub coupler 1002'. In yet another embodiment, the waveguide 1004'can propagate substantially or completely inside the stub coupler 1002'. In this latter embodiment, the waveguide 1004'is at the end of the stub coupler 1002' (such as the tapered end shown in FIG. 9) for coupling to a transmission medium such as wire 702 in FIG. Can be radiated in.

It will be further understood that other configurations of transmitter / receiver device 1006 are possible. For example, as shown by reference numeral 1000'' in FIG. 10B, a hollow metal waveguide of transmitter / receiver device 1006'' (corresponding circuit section not shown) provides a stub coupler 1002. Without using it, it can be arranged tangentially or parallel to the outer surface of the transmission medium such as the electric wire 702 in FIG. 4 (with or without a gap). In this embodiment, the waveguide generated by the transmitter / receiver device 1006'' is coupled to the surface of wire 702 in basic mode (eg, symmetric mode) and / or non-basic mode (eg, asymmetric mode). A waveguide 908 in one or more wave propagation modes including) can be guided on the wire 702. In another embodiment, wire 702 can be positioned inside a hollow metal waveguide of transmitter / receiver device 1006''' (corresponding circuitry not shown), thereby wire 702. Axis is aligned coaxially (or non-coaxially) with the axis of the hollow metal waveguide without the use of the stub coupler 1002 – reference numeral 1000'in Figure 10B. See''. In this embodiment, the waveguide generated by the transmitter / receiver device 1006''' is coupled to the surface of wire 702 in basic mode (eg, symmetric mode) and / or non-basic mode (eg, asymmetric). Waveguide 908 in one or more wave propagation modes, including mode), can be guided onto the wire.

In the embodiments of 1000'' and 1000'''', in the case of the wire 702 having an insulating outer surface, the waveguide 908 propagates partially on the outer surface of the insulator and partially inside the insulator. Can be done. In embodiments, the waveguide can propagate substantially or completely over the outer surface of the insulator, or substantially or completely inside the insulator. In the 1000'' and 1000'''implements, in the case of the bare conductor wire 702, the waveguide 908 may propagate partially on the outer surface of the conductor and partially inside the conductor. it can. In another embodiment, the waveguide can propagate substantially or completely over the outer surface of the conductor.

Here, with reference to FIG. 11, block diagram 1100 showing an example non-limiting embodiment of a double stub coupler is shown. In particular, the double bonder design is presented for use with transmit devices such as transmit device 101 or 102 presented in connection with FIG. In one embodiment, two or more couplers (such as stub couplers 1104 and 1106) can be positioned around wire 1102 to receive the waveguide 1108. In one embodiment, one coupler is sufficient to receive the waveguide 1108. In that case, the waveguide 1108 couples to the coupler 1104 and propagates as a waveguide 1110. If the field structure of the waveguide 1108 vibrates or undulates around the wire 1102 due to a particular waveguide mode or various external factors, the coupler 1106 is arranged so that the waveguide 1108 couples to the coupler 1106. be able to. In some embodiments, waveguides that may oscillate or rotate around wire 1102, guided in different directions, or, for example, orientation-dependent lobes and / or nulls or other non-asymmetrical ones. In order to receive a waveguide having a basic mode or a higher order mode, four or more couplers can be arranged around a part of the wire 1102, for example at 90 degrees to each other or at different intervals. However, it will be appreciated that less than four or more couplers may be placed around a portion of wire 1102 without departing from the exemplary embodiment.

Although the couplers 1106 and 1104 are shown as stub couplers, any other coupler design described herein, including arc couplers, antenna or horn couplers, magnetic couplers, etc., can be used as well. Please note that there is. Also, some exemplary embodiments have presented a plurality of couplers around at least a portion of wire 1102, wherein the plurality of couplers is a single coupling having multiple coupler subcomponents. It will also be understood that it can be considered part of the instrument system. For example, two or more couplers can be manufactured as a single system that can be installed around the wires in a single installation, whereby the couplers are pre-positioned according to that single system. Or adjustable with respect to each other (manually or automatically using a controllable mechanism such as a motor or other actuator).

The receiver coupled to the couplers 1106 and 1104 can combine the signals received from both couplers 1106 and 1104 using diversity synthesis to maximize signal quality. In other embodiments, if either the couplers 1104 or 1106 receives a transmission above a predetermined threshold, the receiver may use selective diversity when deciding which signal to use. it can. Further, although reception by a plurality of couplers 1106 and 1104 is shown, transmission by couplers 1106 and 1104 having the same configuration can be performed in the same manner. In particular, a wide range of multi-input multi-output (MIMO) transmission / reception techniques can be used for transmissions such as the transmission device 101 or 102 presented in connection with FIG. 1 including multiple transmitters / receivers and multiple couplers. is there.

It should be noted that the graphic representations of the waves 1108 and 1110 are only presented to illustrate the principle by which the waveguide 1108 guides or otherwise sends the waves 1110 onto the coupler 1104. The actual electric and magnetic fields generated as a result of such wave propagation are the frequencies used, the design of the coupler 1104, the dimensions and composition of the wire 1102, and its surface properties, insulation if present, ambient environment. It can be changed according to the electromagnetic characteristics of.

Here, with reference to FIG. 12, a block diagram 1200 showing a non-limiting embodiment of an example of a repeater system is shown. In particular, the repeater device 1210 for use in a transmitting device such as the transmitting device 101 or 102 presented in connection with FIG. 1 is presented. In this system, waveguide 1205 propagating along wire 1202 is extracted by coupler 1204 as wave 1206 (eg, as waveguide) and then boosted or reproduced by repeater device 1210 as wave 1216 (eg, as wave 1216). The two couplers 1204 and 1214 can be placed near wire 1202 or other transmission medium so that they are delivered over the coupler 1214 (as waveguides). The wave 1216 can then be sent onto the wire 1202 and continue to propagate along the wire 1202 as a waveguide 1217. In one embodiment, the repeater device 1210 receives at least a portion of the power utilized for boosting or reproduction, for example, if the wire 1202 is a power line or otherwise includes a power line, through magnetic field coupling with the wire 1202. be able to. Couplers 1204 and 1214 are shown as stub couplers, but so do any other type of coupler design described herein, such as arc couplers, antenna or horn couplers, or magnetic couplers. Please note that it can be used for.

In some embodiments, the repeater device 1210 can reproduce the transmission associated with the wave 1206, and in other embodiments, the repeater device 1210 extracts data or other signal from the wave 1206 and its Such data or signals are supplied to another network and / or one or more other devices as communication signals 110 or 112, and / or communication signals 110 or 112 are supplied to another network and / or one or more. A communication interface 205 receiving from another device can be included, and a waveguide 1216 in which the received communication signal 110 or 112 is embedded can be transmitted. In the repeater configuration, the receiver waveguide 1208 can receive the waves 1206 from the coupler 1204, and the transmitter waveguide 1212 can transmit the waveguide 1216 as the waveguide 1217 onto the coupler 1214. Amplifies the signal embedded in the waveguide 1206 and / or the waveguide 1216 itself between the receiver waveguide 1208 and the transmitter waveguide 1212 to compensate for signal loss and other inefficiencies associated with waveguide communication. Or the signal can be received and processed, and the data contained therein can be extracted and regenerated for transmission. In one embodiment, receiver waveguide 1208 extracts data from the signal, processes the data, corrects the data error using, for example, an error correction code, and is updated with the corrected data. It can be configured to reproduce the signal. The transmitter waveguide 1212 can then transmit the waveguide 1216 in which the updated signal is embedded. In one embodiment, the signal embedded in the waveguide 1206 is extracted from the transmission and processed into another network and / or one or more other devices via the communication interface 205 as the communication signal 110 or 112. Can communicate with. Similarly, the communication signal 110 or 112 received by the communication interface 205 can be inserted into the transmission of the waveguide 1216 generated by the transmitter waveguide 1212 and transmitted to the coupler 1214.

Note that FIGS. 12 show waveguide transmissions 1206 and 1216 entering from the left and exiting to the right, respectively, for simplicity only and not intended to be limiting. In other embodiments, the receiver waveguide 1208 and the transmitter waveguide 1212 can also serve as transmitters and receivers, respectively, which allows the repeater device 1210 to be bidirectional.

In one embodiment, the repeater device 1210 can be placed where there are intermittent or obstacles on wire 1202 or other transmission medium. If the wire 1202 is a power line, these obstacles can include transformers, connections, utility poles, and other such power line devices. The repeater device 1210 can facilitate the waveguide (eg, surface waves) to overcome these obstacles on the line and at the same time boost the transmitted power. In other embodiments, the coupler can be used to overcome obstacles without the use of repeater devices. In that embodiment, both ends of the coupler can be connected or fixed to a wire, thereby providing a path for the waveguide to proceed unobstructed by obstacles.

Here, with reference to FIG. 13, a block diagram 1300 of a non-limiting embodiment of an example of a bidirectional repeater according to the various aspects described herein is shown. In particular, the bidirectional repeater device 1306 is presented for use in a transmitting device such as the transmitting device 101 or 102 presented in connection with FIG. Although the coupler is shown as a stub coupler, any other coupler design described herein, including arc couplers, antenna or horn couplers, magnetic couplers, etc., can be used as well. Please note that. The bidirectional repeater 1306 can utilize the diversity path in the presence of two or more wires or other transmission media. Waveguide transmission has different transmission and coupling efficiencies on different types of transmission media such as insulated wire, non-insulated wire, or other types of transmission media, and weather and other atmospheres when exposed to additional elements. It may be advantageous to selectively transmit on different transmission media at specific times, as it can be affected by the situation. In various embodiments, the various transmission media may be referred to as primary, secondary, tertiary, etc., regardless of whether or not the designated transmission medium indicates that it is preferred over another transmission medium.

In the embodiments shown, the transmission medium includes an insulated or non-insulated wire 1302 and an insulated or non-insulated wire 1304 (referred to herein as wires 1302 and 1304, respectively). The repeater device 1306 uses the receiver coupler 1308 to receive the waveguide traveling along the wire 1302, and reproduces the transmission using the transmitter waveguide 1310 as the waveguide along the wire 1304. In other embodiments, the repeater device 1306 can switch from wire 1304 to wire 1302 or reproduce its transmission along the same path. The repeater device 1306 may include or communicate with such sensors (or the network management system 1601 shown in FIG. 16A) to indicate situations that may affect transmission. Based on the feedback received from the sensor, the repeater device 1306 can make a decision as to whether to keep the transmission along the same wire or to transfer the transmission to another wire.

Here, with reference to FIG. 14, block diagram 1400 is shown showing a non-limiting embodiment of an example of a bidirectional repeater system. In particular, the bidirectional repeater system is presented for use with a transmitting device such as the transmitting device 101 or 102 presented in connection with FIG. Bidirectional repeater systems include waveguide coupled devices 1402 and 1404 that receive and transmit transmissions from distributed antenna systems or other coupled devices located within a backhaul system.

In various embodiments, the waveguide coupled device 1402 can receive transmissions from another waveguide coupled device, the transmission having a plurality of subcarriers. The diplexer 1406 can separate the transmission from other transmissions and send the transmission to a low noise amplifier (“LNA”) 1408. The frequency mixer 1428, with the support of the local oscillator 1412, transmits its transmission (in some embodiments, in the millimeter wave band or about 38 GHz) to the cellular band (about 1.9 GHz) in the case of a distributed antenna system. Can be shifted downwards to lower frequencies, such as the original frequency, or other frequencies in the case of backhaul systems. An extractor (or demultiplexer) 1432 extracts a signal on the subcarrier, sends the signal to output component 1422, and optionally amplifies, buffers, or separates it with a power amplifier 1424 and couples it to communication interface 205. be able to. Communication interface 205 further processes the signal received from the power amplifier 1424, or otherwise transmits such signal to other devices such as base stations, mobile devices, buildings, etc. via a wireless or wired interface. can do. For signals that are not extracted at this location, the extractor 1432 can redirect them to another frequency mixer 1436, where in the frequency mixer 1436 the signals are used to modulate the carrier waves produced by the local oscillator 1414. Be done. The carrier is sent along with its subcarrier to a power amplifier (“PA”) 1416 and retransmitted by the waveguide coupling device 1404 via the diplexer 1420 to another system.

The LNA1426 can be used to amplify, buffer, or separate the signal received from the communication interface 205, which in turn can transmit the signal to the multiplexer 1434, which receives from the waveguide coupling device 1404. The signal that was being used is fused with that signal. The signal received from the coupling device 1404 is split by the diplexer 1420, then passed through the LNA 1418, and the frequency is shifted downward by the frequency mixer 1438. When the signal is combined by the multiplexer 1434, the frequency is shifted upward by the frequency mixer 1430, then boosted by the PA 1410 and transmitted by the waveguide coupling device 1402 to another system. In one embodiment, the bidirectional repeater system may be merely a repeater without an output device 1422. In this embodiment, the multiplexer 1434 is not utilized and the signal from the LNA 1418 is sent to the mixer 1430 as described above. It will be appreciated that in some embodiments, the bidirectional repeater system can be implemented with two different and separate unidirectional repeaters. In an alternative embodiment, the bidirectional repeater system can be a booster or can perform retransmissions without any other downshifts and upshifts. In practice, in an exemplary embodiment, retransmissions include receiving a signal or waveguide and some signal or waveguide processing or shaping, filtering, and / or amplification prior to retransmission of the signal or waveguide. It can be based on what you do.

Here, with reference to FIG. 15, block diagram 1500 showing a non-limiting embodiment of an example of a waveguide communication system is shown. This figure shows an exemplary environment in which a waveguide communication system such as the waveguide communication system presented in connection with FIG. 1 can be used.

Backhaul networks that link communication cells (eg, microcells and macrocells) to network devices in the core network expand accordingly to provide network connectivity to additional base station devices. Similarly, an extended communication system that links a base station device to a distributed antenna is desirable in order to provide network connectivity to the distributed antenna system. Waveguide communication systems 1500, such as those shown in FIG. 15, can be provided to allow alternative, augmented, or additional network connections, and waveguide coupling systems include single line transmission lines (eg, utilities). It operates as a line), can be used as a waveguide, and / or transmits and / or transmits waveguide (eg, surface wave) communication on a transmission medium such as an electric wire that operates otherwise to induce the transmission of electromagnetic waves. Can be provided for reception.

The waveguide communication system 1500 provides a first instance 1550 of a distributed system comprising one or more base station devices (eg, base station device 1504) communicably coupled to a central office 1501 and / or macrocell site 1502. Can include. The base station device 1504 can be connected to the macrocell site 1502 and the central office 1501 via a wired connection (eg, fiber and / or cable) or a wireless connection (eg, microwave wireless connection). A second instance of the distributed system, 1560, can be used to provide wireless voice and data services to mobile devices 1522 and residential and / or commercial facilities 1542 (referred to herein as facility 1542). System 1500 may have additional instances 1550 and 1560 of a distributed system that provide voice and / or data services to mobile devices 1522-1524 and facilities 1542, as shown in FIG.

Macrocells, such as the macrocell site 1502, can have or share a dedicated connection to the mobile network and base station device 1504, and / or can use another connection. Media content can be distributed using the central office 1501 and / or Internet service provider (ISP) services can be provided to mobile devices 1522-1524 and facilities 1542. The central office 1501 receives media content from a collection of satellites 1530 (one of which is shown in FIG. 15) or another content source and its media content via a first instance 1550 and a second instance 1560 of the distributed system. Such content can be delivered to mobile devices 1522-1524 and facilities 1542. The central office 1501 can also be communicably coupled to the Internet 1503, thereby providing Internet data services to mobile devices 1522-1524 and facilities 1542.

The base station device 1504 can be mounted or mounted on a utility pole 1516. In other embodiments, the base station device 1504 may be near the transformer and / or elsewhere near the power line. The base station device 1504 can facilitate the connection of the mobile devices 1522 and 1524 to the mobile network. Antennas 1512 and 1514 mounted on or near the electric poles 1518 and 1520, respectively, receive signals from base station device 1504 and are more than where antennas 1512 and 1514 are located at or near base station device 1504. These signals can be transmitted to mobile devices 1522 and 1524 over a much larger area.

Note that FIG. 15 displays three utility poles with one base station device in each instance 1550 and 1560 of the distributed system for simplicity. In other embodiments, the utility pole 1516 may have a larger number of base station devices, with more utility poles having connections connected to distributed antennas and / or facilities 1542.

The transmitting device 1506, such as the transmitting device 101 or 102 presented in connection with FIG. 1, transmits a signal from the base station device 1504 to the antennas 1512 and 1514 via a utility or power line connecting the utility poles 1516, 1518, and 1520. be able to. To transmit the signal, the radio source and / or transmitting device 1506 upconverts the signal from base station device 1504 (eg, via frequency mixing) or microwaves the signal from base station device 1504. Converted to another band signal, the transmitting device 1506 sends out a microwave band wave, which is as a waveguide traveling along a utility line or other wire as described in the previous embodiment. Propagate. In the utility pole 1518, another transmitting device 1508 can receive the waveguide (and optionally amplify the waveguide as needed or desired, or as a repeater that receives and regenerates the waveguide. Can operate), transfer as waveguide on utility lines or other wires. The transmitting device 1508 extracts a signal from the microwave band waveguide and shifts its frequency downwards, or otherwise the original cellular band frequency (eg, 1.9 GHz or other defined cellular frequency) or another. It can also be converted to a cellular (or non-cellular) band frequency. The antenna 1512 can wirelessly transmit the downwardly shifted signal to the mobile device 1522. The process can be repeated by the transmitting device 1510, the antenna 1514, and the mobile device 1524 as needed or desired.

Transmissions from mobile devices 1522 and 1524 can also be received by antennas 1512 and 1514, respectively. The transmitting devices 1508 and 1510 shift the cellular band signal upward to the microwave band or convert it to something else, and transmit the signal over the power line as a waveguide (eg, surface wave or other electromagnetic wave) transmission to the base station device 1504. Can be sent to.

The media content received by the central office 1501 can be supplied to the second instance 1560 of the distributed system via the base station device 1504 and distributed to the mobile device 1522 and the facility 1542. The transmitting device 1510 can be connected to the facility 1542 by one or more wired or wireless interfaces. One or more wired connections are not limited to, but are not limited to, other suitable wired lines, delivering power lines, coaxial cables, fiber cables, twisted pair cables, waveguide transmission media, or media content and / or providing Internet services. Can include media. In an exemplary embodiment, the wired connection from the transmitting device 1510 is one or more corresponding service area interfaces (SAI-not shown) or one or more ultrafast digital subscriber lines located in a pedestal. Can be communicatively coupled to a (VDSL) modem, each SAI or pedestal will service a portion of facility 1542. A VDSL modem can be used to selectively deliver media content to a gateway (not shown) located at facility 1542 and / or provide Internet services. The SAI or pedestal can also be communicably coupled to the facility 1542 via wired media such as power lines, coaxial cables, fiber cables, twisted pair cables, waveguide transmission media, or other suitable wired media. In another exemplary embodiment, the transmitting device 1510 can be communicably directly coupled to the facility 1542 without an intermediate interface such as SAI or pedestal.

In another exemplary embodiment, the system 1500 may utilize a diversity path, in which two or more transmission lines or other wires are stretched between utility poles 1516, 1518 and 1520 (eg, for example. Redundant transmission from the base station / macrocell site 1502 (such as two or more wires between utility poles 1516 and 1520) is transmitted downstream on the surface of the transmission line or other wires as a waveguide. The transmission line or other wire can be either insulated or non-insulated, and depending on the environmental conditions that cause transmission loss, the coupling device selectively receives signals from the insulated or non-insulated transmission line or other wire. can do. The choice can be based on measurements of the signal-to-noise ratio of the wire or can be based on identified weather / environmental conditions (eg, moisture detectors, weather forecasts, etc.). Using a diversity path with the system 1500 can enable alternative routing capabilities, load balancing, increased load handling, simultaneous bidirectional or synchronous communication, spectral spread communication, and the like.

Note that the use of transmitting devices 1506, 1508, and 1510 in FIG. 15 is merely an example, and other uses are possible in other embodiments. For example, the transmitting device can be used in a backhaul communication system that provides a network connection to the base station device. Transmission devices 1506, 1508, and 1510 can be used in many situations where it is desirable to transmit waveguides over wires, whether insulated or not. Transmitting devices 1506, 1508, and 1510 are more than other coupled devices due to lack of contact with wires capable of carrying high voltages or due to limited physical and / or electrical contact. It's an excellent improvement. The transmitting device should be away from the wire (eg, for example, unless it comes into electrical contact with the wire, so that the dielectric acts as an insulator, allowing for an inexpensive, easy, and / or less complex installation. Can be placed (away from the wires) and / or placed on the wires. However, as mentioned above, in configurations where the wires utilize, for example, telephone networks, cable television networks, broadband data services, fiber optic communication systems or other networks that utilize low voltage or have isolated transmission lines. , Conductive or non-dielectric couplers can be utilized.

Although the base station device 1504 and the macrocell site 1502 are exemplified in the embodiment, it should be further noted that other network configurations are possible as well. For example, using devices such as access points or other wireless gateways as well, wireless local area networks, wireless personal area networks, or 802.11 protocols, WIMAX protocols, ultra-broadband protocols, Bluetooth® protocols, Zigbee. The communication range of other networks such as other wireless networks operating according to a communication protocol such as a protocol or another wireless protocol can be expanded.

Here, with reference to FIGS. 16A and 16B, a block diagram showing a non-limiting embodiment of an example of a system for managing a power grid communication system is shown. Considering FIG. 16A, the waveguide system 1602 is presented for use in a waveguide communication system such as the system presented in connection with FIG. The waveguide system 1602 can include a transmission device 101 or 102 including a sensor 1604, a power management system 1605, at least one communication interface 205, a transmitter / receiver 210, and a coupler 220.

The waveguide system 1602 can be coupled to the power line 1610 to facilitate waveguide communication according to the embodiments described in the present disclosure. In an exemplary embodiment, the transmitting device 101 or 102 comprises a coupler 220 that induces electromagnetic waves on the surface of the power line 1610 propagating longitudinally along the surface of the power line 1610, as described herein. .. The transmitting device 101 or 102 can also retransmit the electromagnetic wave on the same power line 1610 or function as a repeater for routing the electromagnetic wave between the power lines 1610, as shown in FIGS. 12 and 13.

The transmitting device 101 or 102 operates at, for example, a carrier frequency that propagates a signal operating in the original frequency range along a coupler to induce a corresponding waveguided electromagnetic wave propagating along the surface of the power line 1610. Includes a transmitter / receiver 210 that is configured to either indicate carrier frequency, or upconvert to an electromagnetic wave associated with the carrier frequency. The carrier frequency can be represented by a center frequency having upper and lower cutoff frequencies that define the bandwidth of the electromagnetic wave. The power line 1610 can be an electric wire having a conductive or insulating surface (eg, a single wire or a stranded wire). The transmitter / receiver 210 may also receive a signal from the combiner 220 and downconvert an electromagnetic wave operating at a carrier frequency into a signal at the original frequency.

The signal received by the communication interface 205 of the transmitting device 101 or 102 for up-conversion is not limited to the signal supplied by the central office 1611 via the wired or wireless interface of the communication interface 205, the wired communication interface 205. Alternatively, a signal supplied by the base station 1614 via a wireless interface, a wired or wireless signal transmitted by the mobile device 1620 to the base station 1614 for distribution via a wired or wireless interface of the communication interface 205, a wired or wired communication interface 205. It can include signals supplied by the in-building communication device 1618 via the wireless interface and / or wireless signals supplied to the communication interface 205 by the mobile device 1612 roaming into the wireless communication range of the communication interface 205. As shown in FIGS. 12 and 13, in an embodiment in which the waveguide system 1602 functions as a repeater, the communication interface 205 may or may not be included in the waveguide system 1602.

The electromagnetic waves propagating along the surface of the power line 1610 are modulated to include packets or frames of data that include a data payload and further include networking information (such as header information that identifies one or more destination waveguide systems 1602). And can be formatted. Networking information may be provided by transmitting devices such as the waveguide system 1602 or central office 1611, base station 1614, mobile device 1620, or in-building device 1618, or a combination thereof. Further, the modulated electromagnetic wave can include error correction data in order to reduce signal disturbance. The destination waveguide system 1602 uses networking information and error correction data to detect transmissions directed to the destination waveguide system 1602 and directed to a receive communication device communicatively coupled to the destination waveguide system 1602. Transmissions that include voice and / or data signals can be down-converted and processed using error-corrected data.

Here, referring to the sensor 1604 of the waveguide system 1602, the sensor 1604 includes a temperature sensor 1604a, a disturbance detection sensor 1604b, an energy loss sensor 1604c, a noise sensor 1604d, a vibration sensor 1604e, an environment (for example, weather) sensor 1604f, and / Or may include one or more of 1604 g of image sensors. The temperature sensor 1604a can be the ambient temperature, the temperature of the transmitting device 101 or 102, the temperature of the power line 1610, the temperature difference (eg, between the transmitting devices 101 or 102 and 1610 compared to the set point or baseline, etc.), or any of them. It can be used to measure combinations. In one embodiment, temperature metrics can be collected on a regular basis and reported to network management system 1601 via base station 1614.

The disturbance detection sensor 1604b can perform measurements on the power line 1610 to detect disturbances such as signal reflections that may indicate the presence of downstream disturbances that may interfere with the propagation of electromagnetic waves on the power line 1610. The signal reflection is transmitted on the power line 1610 by the transmission device 101 or 102, which is totally or partially reflected from the disturbance in the power line 1610 located downstream from the transmission device 101 or 102, for example. It can represent the distortion caused by the electromagnetic waves.

Signal reflections can be caused by obstacles on the power line 1610. For example, tree branches can cause electromagnetic reflections when lying on power line 1610 or in the vicinity of power line 1610, which can cause corona discharge. Other obstacles that may cause electromagnetic reflections include, but are not limited to, objects entwined in power line 1610 (eg, clothing, shoes with shoelaces wrapped around power line 1610, etc.), corrosion deposits on power line 1610, Alternatively, ice deposits can be mentioned. Power grid components can also interfere with or interfere with the propagation of electromagnetic waves on the surface of power line 1610. Examples of power grid components that can cause signal reflection include, but are not limited to, transformers and joints connecting connected power lines. The acute-angled power line 1610 may also cause electromagnetic wave reflection.

The disturbance detection sensor 1604b includes a circuit that compares the magnitude of the electromagnetic wave reflection with the magnitude of the original electromagnetic wave transmitted by the transmitting device 101 or 102 to specify the amount of downstream disturbance in the power line 1610 that attenuates the transmission. Can be done. The disturbance detection sensor 1604b can further include a spectrum analyzer circuit that performs spectrum analysis on the reflected wave. Spectral data generated by the spectral analyzer circuit is compared to the spectral profile via pattern recognition, expert systems, curve fitting, matching filtering, or other artificial intelligence, classification, or comparison techniques, eg, spectral data. The type of disturbance can be identified based on the spectral profile that most closely matches. The spectrum profile can be stored in the memory of the disturbance detection sensor 1604b or can be remotely accessed by the disturbance detection sensor 1604b. The profile can include spectral data that models the different disturbances that may be encountered on the power line 1610 and allows the disturbance detection sensor 1604b to identify the disturbances locally. If known, the identification of the disturbance can be reported to the network management system 1601 via base station 1614. The disturbance detection sensor 1604b can also transmit the electromagnetic wave as a test signal by using the transmission device 101 or 102 to specify the round-trip time of the electromagnetic wave reflection. The round-trip time measured by the disturbance detection sensor 1604b can be used to calculate the distance the electromagnetic wave travels to the point of reflection so that the disturbance detection sensor 1604b is on the power line 1610 from the transmitting device 101 or 102. It is possible to calculate the distance to the disturbance downstream of.

The calculated distance can be reported to the network management system 1601 via base station 1614. In one embodiment, the location of the waveguide system 1602 on the power line 1610 may be known to the network management system 1601, which will be used by the network management system 1601 on the power line 1610 based on the known topology of the power network. The location of the disturbance can be identified. In another embodiment, the waveguide system 1602 can provide its location to the network management system 1601 to assist in locating disturbances on the power line 1610. The location of the waveguide system 1602 can be obtained by the waveguide system 1602 from a pre-programmed position of the waveguide system 1602 stored in the memory of the waveguide system 1602, or the waveguide system 1602 is a waveguide. A GPS receiver (not shown) included in system 1602 can be used to locate it.

The power management system 1605 provides energy to the aforementioned components of the waveguide system 1602. The power management system 1605 can receive energy from a solar cell, from a transformer coupled to power line 1610 (not shown), or by induction coupling to power line 1610 or another nearby power line. The power management system 1605 may also include a spare battery and / or a supercapacitor or other capacitor circuit that provides temporary power to the waveguide system 1602. The energy loss sensor 1604c can be used to detect when the waveguide system 1602 has a power loss situation and / or the occurrence of some other malfunction. For example, the energy loss sensor 1604c can be used when there is a defect in the solar cell, a hindrance to the solar cell causing the solar cell to malfunction, a power loss due to a power loss on the power line 1610 and / or a spare battery expired or a supercapacitor. It is possible to detect when the standby power system malfunctions due to a detectable defect in. In the event of a malfunction and / or power loss, the energy loss sensor 1604c can notify the network management system 1601 via base station 1614.

The noise sensor 1604d can be used to measure noise on the power line 1610, which may adversely affect the transmission of electromagnetic waves on the power line 1610. The noise sensor 1604d can detect unexpected electromagnetic interference, noise bursts, or other sources of disturbance that may interfere with the reception of modulated electromagnetic waves on the surface of the power line 1610. Noise bursts can be caused, for example, by corona discharges or other noise sources. The noise sensor 1604d stores the measured noise through an internal database of noise profiles or noise profiles via pattern recognition, expert systems, curve fitting, matching filtering, or other artificial intelligence, classification, or comparison techniques. It can be compared with the noise profile obtained by the waveguide system 1602 from a remotely located database. From comparison, the noise sensor 1604d can identify a noise source (eg, corona discharge, etc.) based on, for example, a noise profile that provides the closest match to the measured noise. The noise sensor 1604d can also detect how noise affects transmission by measuring transmission metrics such as bit error rate, packet loss rate, jitter, and packet retransmission requests. The noise sensor 1604d can report, among other things, noise source identification information, noise generation time, and transmission metrics to the network management system 1601 via base station 1614.

The vibration sensor 1604e can include an accelerometer and / or a gyroscope that detects 2D or 3D vibration on the power line 1610. Vibrations are stored locally in the waveguide system 1602 via pattern recognition, expert systems, curve fitting, matching filtering, or other artificial intelligence, classification, or comparison techniques, or from a remote database by the waveguide system 1602. It can be compared with the vibration profile that can be obtained. Vibration profiles can be used, for example, to distinguish fallen trees from gusts, for example, based on a vibration profile that provides the closest match to the measured vibration. The result of this analysis can be reported to the network management system 1601 via the base station 1614 by the vibration sensor 1604e.

The environmental sensor 1604f can include, among other things, a barometer that measures atmospheric pressure, ambient temperature (which can be provided by the temperature sensor 1604a), wind speed, humidity, wind direction, and rainfall. The environmental sensor 1604f collects raw information and uses it through pattern recognition, expert systems, knowledge base systems, or other artificial intelligence, classification, or other weather modeling and prediction techniques. This information can be processed by comparing with an environment profile that can be obtained from the memory of 1602 or a remote database to predict the weather conditions before they occur. The environmental sensor 1604f can report the raw data and its analysis to the network management system 1601.

The image sensor 1604g can be a digital camera (eg, a charge coupling element or CCD imager, an infrared camera, etc.) that captures an image in the vicinity of the waveguide system 1602. The image sensor 1604g provides an electromechanical mechanism that controls camera movement (eg, actual position or focus / zoom) to inspect power lines 1610 from multiple viewpoints (eg, top, bottom, left, right, etc.). Can include. Alternatively, the image sensor 1604g can be designed so that no electromechanical mechanism is required to acquire multiple viewpoints. The collection and retrieval of imaging data generated by the image sensor 1604g can be controlled by the network management system 1601 or can be autonomously collected by the image sensor 1604g and reported to the network management system 1601.

The waveguide system 1602 is intended to detect, predict, and / or mitigate disturbances that may interfere with the propagation of electromagnetic transmission over power line 1610 (or any other form of electromagnetic transmission medium). Other sensors that may be suitable for collecting telemetry information associated with and / or power line 1610 can be utilized.

Here, with reference to FIG. 16B, block diagram 1650 is a non-limiting example of a system managing the power grid 1653 and a communication system 1655 incorporated or associated with it, according to the various aspects described herein. Embodiments are shown. The communication system 1655 includes a plurality of waveguide systems 1602 coupled to the power line 1610 of the power grid 1653. At least a portion of the waveguide system 1602 used within the communication system 1655 can communicate directly with the base station 1614 and / or the network management system 1601. The waveguide system 1602, which is not directly connected to the base station 1614 or the network management system 1601, passes through the base station 1614 or another downstream waveguide system 1602 connected to the network management system 1601 to the base station 1614 or the network management system 1601. Can engage in communication sessions with any of.

The network management system 1601 can be communicably coupled to the equipment of the utility company 1652 and the equipment of the communication service provider 1654 to provide status information associated with the power network 1653 and communication system 1655 to each entity. The network management system 1601, the equipment of the utility company 1652, and the communication service provider 1654 are used by the utility company personnel 1656 to provide status information and / or to direct personnel to the management of the power network 1653 and / or the communication system 1655. The communication device and / or the communication device used by the communication service provider personnel 1658 can be accessed.

FIG. 17A shows a flow diagram of an example of a non-limiting embodiment of Method 1700 that detects and mitigates disturbances that occur in the communication networks of the systems of FIGS. 16A and 16B. Method 1700 can be initiated in step 1702, where the waveguide system 1602 is embedded in or forms part of a modulated electromagnetic wave or another type of electromagnetic wave traveling along the surface of the power line 1610. To send and receive. The message can be a voice message, streaming video, and / or other data / information exchanged between communication devices communicatively coupled to communication system 1655. In step 1704, the sensor 1604 of the waveguide system 1602 can collect the detection data. In one embodiment, the detection data can be collected in step 1704 before, during, or after the transmission and / or reception of the message in step 1702. In step 1706, the waveguide system 1602 (or the sensor 1604 itself) can affect the communication originating from (eg, transmitted) or received by the waveguide system 1602 from the detection data. It is possible to identify the actual or expected occurrence of disturbances within a sexual communication system 1655. The waveguide system 1602 (or sensor 1604) can process temperature data, signal reflection data, energy loss data, noise data, vibration data, environmental data, or any combination thereof to make this identification. The waveguide system 1602 (or sensor 1604) can also detect, identify, estimate, or predict the cause and / or its location of disturbances in communication system 1655. If the disturbance is not detected / identified and predicted / estimated in step 1708, the waveguide system 1602 can proceed to step 1702 and be incorporated into a modulated electromagnetic wave traveling along the surface of the power line 1610. Or continue to send and receive messages that form part of it.

If the disturbance is detected / identified or the occurrence is predicted / estimated in step 1708, the waveguide system 1602 proceeds to step 1710, where the disturbance may adversely affect the transmission or reception of messages in communication system 1655. Determine if there is (or, alternative, is or is likely to have an adverse effect). In one embodiment, the duration threshold and the frequency threshold can be used in step 1710 to identify when disturbances adversely affect communication in communication system 1655. For illustrative purposes only, it is assumed that the duration threshold is set to 500 ms, while the frequency threshold is set to 5 disturbances during the 10 second observation period. Therefore, disturbances with a duration longer than 500 ms trigger a duration threshold. Furthermore, disturbances that occur more than 6 times during a time interval of 10 seconds trigger an occurrence frequency threshold.

In one embodiment, disturbances can be considered to adversely affect signal integrity in communication system 1655 if only the duration threshold is exceeded. In another embodiment, disturbances can be considered to adversely affect signal integrity in communication system 1655 if both duration and frequency thresholds are exceeded. Therefore, the latter embodiment is more conservative than the former embodiment with respect to the classification of disturbances that adversely affect signal integrity in communication system 1655. It will be appreciated that by way of exemplary embodiments, many other algorithms and related parameters and thresholds may be utilized in step 1710.

Referring again to method 1700, in step 1710, if the disturbance detected in step 1708 does not meet the adverse communication conditions (eg, neither the duration threshold nor the frequency threshold is exceeded), the waveguide system 1602 Step 1702 can be taken to continue processing the message. For example, if the disturbance detected in step 1708 has a duration of 1 ms and one occurrence during a time period of 10 seconds, neither threshold is exceeded. Therefore, such disturbances can be considered as having only a slight effect on signal integrity in communication system 1655 and are therefore not flagged as disturbances that need mitigation. Although not flagged, the occurrence of disturbances, their time of occurrence, their frequency of occurrence, spectral data, and / or other useful information can be reported to the network management system 1601 as telemetry data for monitoring purposes.

Seeing step 1710 again, on the other hand, if the disturbance meets the adversely affected communication conditions (eg, exceeding one or both thresholds), the waveguide system 1602 proceeds to step 1712 to network the incident. It can be reported to system 1601. The report is the raw detection data collected by the sensor 1604, the description of the disturbance, the time of occurrence of the disturbance, the frequency of occurrence of the disturbance, the location associated with the disturbance, the bit rate error, the packet loss, if known by the waveguide system 1602. It can include parameter readings such as rate, retransmission request, jitter, wait time and the like. If the disturbance is based on predictions by one or more sensors of the waveguide system 1602, the report will report the type of disturbance expected and, if predictable, the predicted occurrence time of the disturbance, and the prediction will be the sensor 1604 of the waveguide system 1602. Based on the past detection data collected by, it can include the predicted frequency of occurrence of the predicted disturbance.

In step 1714, the network management system 1601 can determine a mitigation, bypass, or remediation technique so that the technique reroutes traffic and bypasses the disturbance if it can locate the disturbance. May include instructing the waveguide system 1602. In one embodiment, the waveguide coupling device 1402 that detects the disturbance connects the waveguide system 1602 from the primary power line affected by the disturbance to the secondary power line, and the waveguide system 1602 retransmits the traffic to a different transmission medium. Repeaters, such as those shown in FIGS. 13 and 14, can be instructed to route and avoid disturbances. In one embodiment in which the waveguide system 1602 is configured as a repeater, the waveguide system 1602 can itself perform rerouting of traffic from the primary power line to the secondary power line. For bidirectional communication (eg, full-duplex or half-duplex communication), the repeater may be configured to reroute traffic from the secondary power line back to the primary power line for processing by the waveguide system 1602. Please pay more attention to.

In another embodiment, the waveguide system 1602 temporarily redirects traffic from the primary power line to the secondary power line to avoid disturbance, and a first repeater and upstream of the disturbance to return to the primary power line. Traffic can be redirected by directing a second repeater downstream of the disturbance. It should be further noted that in the case of two-way communication (eg, full-duplex or half-duplex communication), the repeater may be configured to reroute the traffic from the secondary line to the primary line again.

To avoid interruptions to existing communication sessions occurring on the secondary power line, the network management system 1601 utilizes the unused time slots and / or frequency bands of the secondary power line for data and / or voice traffic. Can be instructed to redirect the waveguide system 1602 away from the primary power line and instruct the repeater to bypass the disturbance.

In step 1716, while the traffic is being rerouted to avoid disturbances, the network management system 1601 is detected and known to the equipment of utility company 1652 and / or the equipment of communication service provider 1654. If so, the location can be notified and these devices can then notify the personnel of the utility company 1656 and / or the personnel of the communications service provider 1658. On-site personnel from either party may respond to and resolve the disturbance at the identified disturbance location. When the disturbance is eliminated or otherwise mitigated by the personnel of the utility company and / or the personnel of the communication service provider, such personnel are communicably coupled to the equipment in the field (eg, network management system 1601). Computers, smartphones, etc.) and / or the equipment of utility companies and / or the equipment of communication service providers can be used to notify each company and / or network management system 1601. The notification can include a description of how the disturbance was mitigated and any changes to the power line 1610 that may change the topology of communication system 1655.

When the disturbance is resolved (as determined in Judgment 1718), the network management system 1601 restores the previous routing configuration used by the waveguide system 1602, or the restoration method used to mitigate the disturbance. If a new network topology for communication system 1655 is generated by, the waveguide system 1602 can be instructed in step 1720 to route traffic according to the new routing configuration. In another embodiment, the waveguide system 1602 can be configured to monitor disturbance mitigation by transmitting a test signal over power line 1610 to detect when the disturbance is gone. When the waveguide system 1602 detects that there is no disturbance and determines that the network topology of the communication system 1655 has not been changed, the routing configuration can be autonomously restored without the assistance of the network management system 1601. Alternatively, a new routing configuration that matches the new discovered network topology can be utilized.

FIG. 17B shows a flow diagram of a non-limiting embodiment of an example of method 1750 that detects and mitigates disturbances that occur in the communication networks of the systems of FIGS. 16A and 16B. In one embodiment, method 1750 can be initiated in step 1752, where the network management system 1601 receives maintenance information associated with the maintenance plan from the equipment of utility company 1652 or the equipment of communication service provider 1654. In step 1754, the network management system 1601 can identify the maintenance activities performed during the maintenance plan from the maintenance information. From these activities, the network management system 1601 was designed for disturbances resulting from maintenance (eg, planned replacement of power line 1610, planned replacement of waveguide system 1602 on power line 1610, planned replacement of power line 1610 in power grid 1653. Reconstruction, etc.) can be detected.

In another embodiment, the network management system 1601 can receive telemetry information from one or more waveguide systems 1602 in step 1755. The telemetry information is, among other things, the identification information of each waveguide system 1602 that submits the telemetry information, the measured value taken by the sensor 1604 of each waveguide system 1602, and whether it is detected or predicted by the sensor 1604 of each waveguide system 1602. It can include information related to the estimated or actual disturbance, position information associated with each waveguide system 1602, estimated location of the detected disturbance, disturbance identification information, and the like. From the telemetry information, the network management system 1601 can identify the type of disturbance that may be detrimental to the operation of the waveguide, the transmission of electromagnetic waves along the wire surface, or both. The network management system 1601 can also use telemetry information from the plurality of waveguide systems 1602 to separate and identify disturbances. In addition, the network management system 1601 requests telemetry information from the waveguide system 1602 in the vicinity of the affected waveguide system 1602 to locate the disturbance by triangulation and / or other waveguide systems. Disturbance identification can be confirmed by receiving similar telemetry information from 1602.

In yet another embodiment, the network management system 1601 can receive an unplanned activity report from maintenance site personnel in step 1756. Unplanned maintenance can be performed as a result of unplanned site calls or as a result of unexpected site problems found during on-site calls or planned maintenance activities. The activity report is a change to the topology configuration of the power grid 1653 resulting from the field personnel addressing problems found in the communication system 1655 and / or the power grid 1653 (its change to one or more waveguide systems 1602). (Replacement or repair, etc.), mitigation of disturbance to be performed in the event of disturbance, etc. can be identified.

In step 1758, the network management system 1601 predicts from the reports received in accordance with steps 1752-1756 whether or not a disturbance has occurred based on the maintenance plan, or whether or not a disturbance has occurred based on telemetry data. It can be determined whether or not the disturbance was caused by unplanned maintenance identified in the field activity report. From these optional reports, the network management system 1601 determines whether the detected or predicted disturbance requires rerouting of traffic by the affected waveguide system 1602 or another waveguide system 1602 of communication system 1655. Can be determined.

If a disturbance is detected or predicted in step 1758, the network management system 1601 can proceed to step 1760 and the network management system 1601 has one or more waveguides to reroute the traffic to bypass the disturbance. You can instruct system 1602. If the disturbance is permanent due to a permanent topology change in the power grid 1653, the network management system 1601 can proceed to step 1770 and skip steps 1762, 1764, 1766, and 1772. At step 1770, the network management system 1601 can instruct one or more waveguide systems 1602 to use a new routing configuration that fits the new topology. However, if the disturbance is detected from the telemetry information provided by one or more waveguide systems 1602, the network management system 1601 is known to the maintenance personnel of the utility company 1656 or the communications service provider 1658 of the location of the disturbance. In some cases, the type of disturbance and relevant information that such personnel may be useful in mitigating the disturbance can be notified. If the disturbance is expected to be due to maintenance activity, network management system 1601 should reconfigure the traffic route with a given plan (consistent with the maintenance plan) to avoid the disturbance caused by the maintenance activity during the maintenance plan. Can be directed to one or more waveguide systems 1602.

Returning to step 1760 again and completing step 1760, the process can continue to step 1762. At step 1762, the network management system 1601 can monitor when disturbances are mitigated by field personnel. Disturbance mitigation is submitted to the network management system 1601 by field personnel via a communication network (eg, a cellular communication system) using field equipment (eg, a laptop computer or handheld computer / device). Can be detected in step 1762 by analyzing the report of. If field personnel report that the disturbance has been mitigated, the network management system 1601 can proceed to step 1764 to determine from the field report whether the topology change was necessary to mitigate the disturbance. Topology changes can include rerouting the power lines 1610, reconfiguring the waveguide system 1602 to utilize different power lines 1610, and otherwise bypassing disturbances using alternative links. If a topology change is made, the network management system 1601 can instruct one or more waveguide systems 1602 to use a new routing configuration adapted to the new topology in step 1770.

However, if the topology change was not reported by field personnel, the network management system 1601 could proceed to step 1766, and the network management system 1601 would send a test signal and the routing used prior to disturbance detection. One or more waveguide systems 1602 can be instructed to test the configuration. The test signal can be transmitted to the affected waveguide system 1602 in the vicinity of the disturbance. The test signal can be used to determine if signal disturbances (eg, electromagnetic reflections) are detected by any waveguide system 1602. If the test signal confirms that the previous routing configuration is no longer subject to previously detected disturbances, the network management system 1601 will install the previous routing configuration on the affected waveguide system 1602 in step 1772. Can be instructed to restore. However, if the test signal analyzed by one or more waveguide coupled devices 1402 and reported to the network management system 1601 indicates that the disturbance or new disturbance is present, the network management system 1601 will go to step 1768. Proceed and report this information to field personnel to further address field issues. The network management system 1601 can continue to monitor the disturbance mitigation in step 1762 in this situation.

In the above embodiment, the waveguide system 1602 can be configured to be self-adapting to modification and / or disturbance mitigation of power grid 1653. That is, one or more affected waveguide systems 1602 may be configured to self-monitor disturbance mitigation and reconfigure traffic routes without the need for transmission of instructions by network management system 1601. it can. In this embodiment, one or more self-configurable waveguide systems 1602 can notify the network management system 1601 of the routing choices of the waveguide system 1602, whereby the network management system 1601 communicates. A macro-level view of the communication topology of system 1655 can be maintained.

For simplicity, each process is shown and described as a series of blocks in FIGS. 17A and 17B, respectively, but the subject matter described in the claims is not limited by the order of the blocks and some blocks , It is understood and recognized that they may be performed in a different order than those shown and described herein, and / or in the same manner as other blocks. Moreover, not all blocks shown may be required to implement the methods described herein.

Here, with reference to FIG. 18A, a block diagram showing a non-limiting embodiment of an example of a transmission medium 1800 propagating a waveguided electromagnetic wave is shown. In particular, a further example of the transmission medium 125 presented in connection with FIG. 1 is presented. In one embodiment, the transmission medium 1800 can include a first dielectric material 1802 and a second dielectric material 1804 deposited on the transmission medium 1800. In one embodiment, the first dielectric material 1802 may include a dielectric core (referred to herein as the dielectric core 1802) and the second dielectric material 1804 may be a whole or partial dielectric core. It can include a cladding or shell (referred to herein as the dielectric foam 1804), such as a dielectric foam surrounding the. In one embodiment, the dielectric core 1802 and the dielectric foam 1804 can (but need not) be aligned coaxially with each other. In one embodiment, the combination of the dielectric core 1802 and the dielectric foam 1804 can be bent or curved by at least 45 degrees without damaging the materials of the dielectric core 1802 and the dielectric foam 1804. In one embodiment, the outer surface of the dielectric foam 1804 is further surrounded in whole or in part by a third dielectric material 1806 that can function as a jacket (referred to herein as the jacket 1806). Can be done. The outer cover 1806 can avoid exposure of the dielectric core 1802 and the dielectric foam 1804 to an environment (eg, water, soil, etc.) that can adversely affect the propagation of electromagnetic waves.

The dielectric core 1802 can include, for example, a high density polyethylene material, a high density polyurethane material, or other suitable dielectric material. The dielectric foam 1804 can include, for example, foamed plastic materials such as polyethylene foam materials or other suitable dielectric materials. The outer cover 1806 can include, for example, a polyethylene material or an equivalent material. In one embodiment, the dielectric constant of the dielectric foam 1804 can be lower (or substantially lower) than the dielectric constant of the dielectric core 1802. For example, the permittivity of the dielectric core 1802 can be about 2.3, while the permittivity of the dielectric foam 1804 can be about 1.15 (slightly higher than the permittivity of air).

The dielectric core 1802 receives a signal in the form of an electromagnetic wave from a transmitter or other coupling device described herein that can be configured to emit an electromagnetic wave guided over the transmission medium 1800. Can be used for. In one embodiment, the transmission medium 1800 can be coupled to a hollow waveguide 1808 constructed as, for example, a circular waveguide 1809, which can receive electromagnetic waves from a radiating device such as a stub antenna (not shown). it can. Therefore, the hollow waveguide 1808 can induce electromagnetic waves waveguided to the dielectric core 1802. In this configuration, the electromagnetic wave guided is coupled to the waveguide or the dielectric core 1802 by the dielectric core 1802 and propagates in the longitudinal direction along the dielectric core 1802. By adjusting the electronic circuit of the transmitter, the operating frequency of the electromagnetic wave is selected so that the field intensity profile 1810 of the waveguided electromagnetic wave extends slightly (or does not extend at all) to the outside of the jacket 1806. Can be done.

By maintaining most (if not all) of the field strength of the waveguided electromagnetic waves within the portions of the dielectric core 1802, the dielectric foam 1804 and / or the jacket 1806, the transmission medium 1800 propagates internally. It can be used in harsh environments without adversely affecting the propagation of electromagnetic waves. For example, the transmission medium 1800 can be buried in the soil without adversely affecting (or substantially without) the waveguided electromagnetic waves propagating through the transmission medium 1800. Similarly, the transmission medium 1800 can be exposed to water (eg, placed in rain or water) without adversely affecting (or substantially without) the waveguided electromagnetic waves propagating through the transmission medium 1800. it can. In one embodiment, the propagation loss of the waveguided electromagnetic wave in the above embodiment can be 1 dB to 2 dB or more per meter at an operating frequency of 60 GHz. Other propagation losses may be possible depending on the operating frequency of the waveguided electromagnetic waves and / or the material used for the transmission medium 1800. Further, depending on the material used to construct the transmission medium 1800, the transmission medium 1800 adversely affects the waveguided electromagnetic waves propagating through the dielectric core 1802 and the dielectric foam 1804 in some embodiments. It can be flexed laterally without (or substantially without) reaching.

FIG. 18B shows a transmission medium 1820 that differs from the transmission medium 1800 of FIG. 18A but still provides a further example of the transmission medium 125 presented in connection with FIG. The transmission medium 1820 indicates a similar reference code to a similar element of the transmission medium 1800 of FIG. 18A. In contrast to the transmission medium 1800, the transmission medium 1820 includes a conductive core 1822 having an insulating layer 1823 that completely or partially surrounds the conductive core 1822. The combination of the insulating layer 1823 and the conductive core 1822 is referred to herein as the insulating conductor 1825. In the figure of FIG. 18B, the insulating layer 1823 is entirely or partially covered by a dielectric foam 1804 and a jacket 1806 that can be constructed from the materials described above. In one embodiment, the insulating layer 1823 can include a dielectric material such as polyethylene having a dielectric constant (eg, 2.3) higher than the dielectric constant of the dielectric foam 1804 (eg, 1.15). In one embodiment, the components of the transmission medium 1820 can (but need not be) coaxially aligned. In one embodiment, a hollow waveguide 1808 with a metal plate 1809 that may (but does not have to be) separate from the insulating layer 1823 is used to substantially propagate over the outer surface of the insulating layer 1823. Although the electromagnetic waves generated can be transmitted, other coupling devices as described herein can be utilized as well. In one embodiment, the waveguided electromagnetic wave can be coupled to the waveguide or the insulating layer 1823 by the insulating layer 1823 sufficiently to guide the electromagnetic wave in the longitudinal direction along the insulating layer 1823. By adjusting the operating parameters of the transmitter, the operating frequency of the wave-guided electromagnetic waves transmitted by the hollow waveguide 1808 produces a wave-guided electromagnetic wave that is substantially confined within the dielectric foam 1804. An electric field strength profile 1824 can be generated so that the wave-guided electromagnetic waves are not exposed to an environment (eg, water, soil, etc.) that adversely affects the propagation of the wave-guided electromagnetic waves through the transmission medium 1820. To.

FIG. 18C shows a transmission medium 1830 that differs from the transmission media 1800 and 1820 of FIGS. 18A and 18B, but still provides a further example of the transmission medium 125 presented in connection with FIG. Transmission medium 1830 shows similar reference numerals to similar elements of transmission media 1800 and 1820 of FIGS. 18A and 18B, respectively. In contrast to the transmission media 1800 and 1820, the transmission medium 1830 is bare (or non-insulated) entirely or partially surrounded by a dielectric foam 1804 and a jacket 1806 that can be constructed from the materials described above. Includes conductor 1832. In one embodiment, the components of the transmission medium 1830 can (but need not be) coaxially aligned. In one embodiment, a hollow waveguide 1808 having a metal plate 1809 coupled to a bare conductor 1832 can be used to deliver a waveguided electromagnetic wave that substantially propagates over the outer surface of the bare conductor 1832. However, other coupled devices as described herein can be utilized as well. In one embodiment, the waveguided electromagnetic wave is coupled to the waveguide or bare conductor 1832 by the bare conductor 1832, sufficient to guide the electromagnetic wave guided longitudinally along the bare conductor 1832. can do. By adjusting the operating parameters of the transmitter, the operating frequency of the wave-guided electromagnetic waves transmitted by the hollow waveguide 1808 produces a wave-guided electromagnetic wave that is substantially confined within the dielectric foam 1804. An electric field strength profile 1834 can be generated, thereby preventing the waveguided electromagnetic waves from being exposed to an environment (eg, water, soil, etc.) that adversely affects the propagation of electromagnetic waves through the transmission medium 1830.

Note that the hollow transmitter 1808 used with the transmission media 1800, 1820, and 1830 of FIGS. 18A, 18B, and 18C, respectively, can be replaced with other transmitters or coupling devices. Further, the electromagnetic wave propagation mode in any of the above embodiments may be a basic mode, a non-basic (or asymmetric) mode, or a combination thereof.

FIG. 18D is a block diagram showing a non-limiting embodiment of an example of a transmission medium bundle 1836 according to various aspects described herein. The transmission medium bundle 1836 can include a plurality of cables 1838 held in place by the flexible sleeve 1839. The plurality of cables 1838 may include multiple instances of cable 1800 of FIG. 18A, multiple instances of cable 1820 of FIG. 18B, multiple instances of cable 1830 of FIG. 18C, or any combination thereof. The sleeve 1839 can include a dielectric material that keeps soil, water, or other external material out of contact with the cables 1838. In one embodiment, a plurality of transmitters, each utilizing a transmitter / receiver similar to that shown in FIG. 10A or other coupling device described herein, selectively radiowaveguided electromagnetic waves in each cable. Electromagnetic waves that can be configured to guide and are guided carry different data (eg, bundles, audio, video, messaging, content, etc.). In one embodiment, by adjusting the operating parameters of each transmitter or other coupling device, each electric field intensity profile of the waveguided electromagnetic wave is completely or substantially within the layer of the corresponding cable 1838. It is trapped and can reduce crosstalk between cables 1838.

In situations where the electric field strength profile of each waveguided electromagnetic wave is not completely or substantially confined within the corresponding cable 1838, crosstalk of the electromagnetic signal is across the two cables shown in FIG. 18E. It can occur between cables 1838, as shown by the associated signal plot. The plot in FIG. 18E shows that when the waveguided electromagnetic waves are induced on the first cable, the electric and magnetic fields emitted by the first cable induce signals on the second cable, causing crosstalk. Show to get. Crosstalk between cables 1838 in FIG. 18D can be reduced using several mitigation options. In one embodiment, as shown in FIG. 18F, an absorbent material 1840 capable of absorbing an electromagnetic field such as carbon is applied to the cable 1838 to polarize each of the electromagnetic waves guided in various polarized states. The crosstalk between cables 1838 can be reduced. In another embodiment (not shown), carbon beads can be added in the gaps between the cables 1838 to reduce crosstalk.

In yet another embodiment (not shown), the diameters of the cables 1838 can be configured differently to change the propagation velocity of the waveguided electromagnetic waves between the cables 1838 and reduce the crosstalk between the cables 1838. .. In one embodiment (not shown), the shape of each cable 1838 can be asymmetric (eg, elliptical) to reduce crosstalk by directing the guided electromagnetic fields of each cable 1838 away from each other. .. In one embodiment (not shown), a filling material, such as a dielectric foam, can be added between the cables 1838 to sufficiently separate the cables 1838 to reduce crosstalk between the cables. In one embodiment (not shown), a longitudinal carbon strip or swirl is applied to the outer surface of the outer cover 1806 of each cable 1838 to reduce the emission of waveguide electromagnetic waves outside the outer cover 1806, thereby the cable. Crosstalk between 1838 can be reduced. In yet another embodiment, each transmitter is configured to deliver a waveguided electromagnetic wave having a different frequency, modulation, wave propagation mode, such as orthogonal frequency, modulation or mode, to reduce crosstalk between cables 1838. can do.

In yet another embodiment (not shown), pairs of cables 1838 can be spirally twisted to reduce crosstalk between pairs and between other cables 1838 in the vicinity of the pairs. In some embodiments, certain cables 1838 can be twisted together, while other cables 1838 can be untwisted to reduce crosstalk between cables 1838. In addition, each pair of twisted cables 1838 has a different pitch (ie, different twist rates, such as the number of twists per meter), between pairs and between other cables 1838 in the vicinity of the pair. Crosstalk can be further reduced. In another embodiment (not shown), a transmitter or other coupling device guides a waveguided electromagnetic wave into the cable 1838 with an electromagnetic field extending beyond the jacket 1806 and in the gap between the cables. Can be configured to reduce crosstalk between cables 1838. Reducing Crosstalk Between Cables 1838 It is proposed that any one of the above embodiments may be combined to further reduce crosstalk between cables 1838.

18G and 18H are block diagrams illustrating a non-limiting embodiment of an example of a transmission medium having an internal waveguide according to the various aspects described herein. In one embodiment, the transmission medium 1841 may include a core 1842. In one embodiment, the core 1842 can be a dielectric core 1842 (eg, polyethylene). In another embodiment, the core 1842 can be an insulated conductor or a non-insulated conductor. The core 1842 can be surrounded by a shell 1844 containing a dielectric foam (eg, a foamed polyethylene material) having a dielectric constant lower than the dielectric constant of the dielectric core or the insulating layer of the conductive core. Due to the difference in dielectric constant, electromagnetic waves can be coupled to the core 1842 and guided. The outer cover 1844 can be covered with a shell outer cover 1845. The shell jacket 1845 can be made of a rigid material (eg, high density plastic) or a high tension material (eg, synthetic fiber). In one embodiment, the shell jacket 1845 can be used to prevent the shell 1844 and core 1842 from being exposed to adverse environments (eg, water, moisture, soil, etc.). In one embodiment, the shell outer cover 1845 is rigid enough to allow the outer surface of the core 1842 to be separated from the inner surface of the shell outer cover 1845, thereby creating a longitudinal gap between the shell outer cover 1854 and the core 1842. Can have. The longitudinal gap can be filled with the dielectric foam of Shell 1844.

The transmission medium 1841 can further include a plurality of outer ring conductors 1846. The outer ring conductor 1846 may be a strand of conductive material woven around the shell outer cover 1845, thereby covering the shell outer cover 1845 in whole or in part. The outer ring conductor 1846 can serve the function of a power line having a feedback electrical path, similar to the embodiments described in the present disclosure that receive a power signal from a source (eg, a transformer, a generator, etc.). In one embodiment, the outer ring conductor 1846 can be covered with a cable jacket 1847 to prevent the outer ring conductor 1846 from being exposed to water, soil, or other environmental factors. The cable jacket 1847 can be made of an insulating material such as polyethylene. The core 1842 can be used as a central waveguide for electromagnetic wave propagation. A signal that induces an electromagnetic wave guided by a core 1842 using a hollow waveguide transmitter 1808, such as the circular waveguide described above, in the same manner as described for embodiments of FIGS. 18A, 18B, and 18C. Can be sent. Electromagnetic waves can be guided by the core 1842 without utilizing the electrical feedback path of the outer ring conductor 1846 or any other electrical feedback path. By adjusting the electronics of transmitter 1808, the operating frequency of the electromagnetic waves can be selected so that the field intensity profile of the waveguided electromagnetic waves extends slightly (or does not extend at all) to the outside of the shell jacket 1845. ..

In another embodiment, the transmission medium 1843 may include a hollow core 1842' surrounded by a shell jacket 1845'. The shell jacket 1845'can have an internal conductive surface or other surface material that allows the hollow core 1842' to be used as a conduit for electromagnetic waves. The shell jacket 1845'can be at least partially covered with the outer ring conductor 1846 described above for the conduction of power signals. In one embodiment, the cable jacket 1847 can be placed on the outer surface of the outer ring conductor 1846 to prevent the outer ring conductor 1846 from being exposed to water, soil, or other environmental factors. The waveguide transmitter 1808 can be used to transmit electromagnetic waves waveguided by the conductive inner surfaces of the hollow core 1842'and the shell jacket 1845'. In one embodiment (not shown), the hollow core 1842'can further include a dielectric foam as described above.

Transmission medium 1841 represents a multipurpose cable that conducts power on an outer ring conductor 1846 using an electrical feedback path and provides communication services through an internal waveguide that includes a combination of core 1842, shell 1844, and shell jacket 1845. be able to. The internal waveguide can be used to transmit or receive electromagnetic waves guided by the core 1842 (without utilizing an electrical feedback path). Similarly, the transmission medium 1843 is a multipurpose cable that uses an electrical feedback path to conduct power on the outer ring conductor 1846 and provides communication services via an internal waveguide that includes a combination of hollow core 1842'and shell jacket 1845'. Can be represented. The internal waveguide can be used to transmit or receive electromagnetic waves guided by the hollow core 1842'and the shell jacket 1845' (without utilizing an electrical feedback path).

It is proposed that the embodiments of FIGS. 18G and 18H may be configured to use a plurality of internal waveguides surrounded by an outer ring conductor 1846. Internal waveguides are configured to use the crosstalk mitigation techniques described above (eg, waveguide twist pairs, waveguides of different structural dimensions, use of quadrupoles in the shell, use of different wave modes, etc.) be able to.

For purposes of illustration only, the transmission media 1800, 1820, 1830, 1836, 1841, and 1843, wherein the cable 1850 is used herein for any one of the transmission media described herein, or multiple instances thereof. With the understanding that it can represent a bundle of cables, it is called cable 1850. For purposes of illustration only, the dielectric cores 1802, insulating conductors 1825, and bare conductors 1832, cores 1842, or hollow cores 1842'of transmission media 1800, 1820, 1830, 1836, 1841, and 1843 are used herein as cables. The 1850 is said to be able to utilize the dielectric cores 1802, insulating conductors 1825, bare conductors 1832, cores 1842, or hollow cores 1842', respectively, of transmission media 1800, 1820, 1830, 1836, 1841, and / or 1843. Under the understanding, they are called transmission media 1852, respectively.

Here, with reference to FIGS. 18I and 18J, a block diagram showing a non-limiting embodiment of an example of a connector configuration that can be used with the cable 1850 is shown. In one embodiment, the cable 1850 can be configured in a female or male connection configuration, as shown in FIG. 18I. The male configuration on the right side of FIG. 18I can be achieved by stripping the dielectric foam 1804 (and the outer cover 1806, if any) so as to expose a portion of the transmission core 1852. The female configuration on the left side of FIG. 18I can be achieved by removing the portion of the transmission core 1852 while maintaining the dielectric foam 1804 (and the outer cover 1806 if present). As described in connection with FIG. 18H, in one embodiment in which the transmission core 1852 is hollow, the male portion of the transmission core 1852 slides into the female configuration on the left side of FIG. 18I to provide the hollow core. It can represent a hollow core with a rigid outer surface that can be aligned together. It should be further noted that in the embodiments of FIGS. 18G and 18H, the outer ring conductor 1846 can be modified to connect the male and female portions of the cable 1850.

Based on the above embodiment, two cables 1850 having a male connector configuration and a female connector configuration can be integrally connected. A sleeve with an adhesive internal lining or shrink packaging material (not shown) is applied to the area of the joint between the cables 1850 to keep the joint in place and exposed (eg to water, soil, etc.). Can be avoided. When the cables 1850 are coupled, the transmission core 1852 of one cable will be in close proximity to the transmission core 1852 of the other cable. The electromagnetic waves propagated by any of the transmission cores 1852 of the cable 1850 traveling from either direction are coaxially aligned with the transmission core 1852 regardless of whether the transmission cores 1852 are in contact with each other. It is possible to cross between non-identical transmission cores 1852 with or without and / or with or without a gap between the transmission cores 1852.

In another embodiment, a splice device 1860 with a female connector configuration at both ends can be coupled to a cable 1850 with a male connector configuration, as shown in FIG. 18J. In an alternative embodiment not shown in FIG. 18J, the splice device 1860 can be configured to have a male connector configuration at both ends that can be coupled to a cable 1850 having a female connector configuration. In another embodiment not shown in FIG. 18J, the splice device 1860 has a male connector configuration and a female connector configuration at opposite ends that can be coupled to a cable 1850 having a female connector configuration and a male connector configuration, respectively. It can be configured as follows. For transmission cores 1852 with hollow cores, the males described in FIG. 18I, regardless of whether the ends of the splice device 1860 are both male, both female, or a combination thereof. It should be further noted that the configuration and female configuration are applicable to the splice device 1860.

The above embodiment of connecting the cables shown in FIGS. 18I and 18J can be applied to each one instance of cable 1838 of the cohesive transmission medium 1836. Similarly, the embodiment shown in FIGS. 18 and 18J can be applied to each one instance of the internal waveguide of a cable 1841 or 1843 having a plurality of internal waveguides.

Here, referring to FIG. 18K, a block showing an example non-limiting embodiment of transmission media 1800', 1800'', 1800''', and 1800'''' propagating a waveguided electromagnetic wave The figure is shown. In one embodiment, the transmission medium 1800'can include a core 1801 and a dielectric foam 1804' divided into sections and covered with a jacket 1806 as shown in FIG. 18K. The core 1801 can be represented by the dielectric core 1802 of FIG. 18A, the insulating conductor 1825 of FIG. 18B, or the bare conductor 1832 of FIG. 18C. Each section of the dielectric foam 1804'can be separated by a gap (eg, air, gas, vacuum, or a substance with a low dielectric constant). In one embodiment, the gap separation between sections of the dielectric foam 1804'can be quasi-random as shown in FIG. 18K, which is dielectric as the electromagnetic wave propagates longitudinally along the core 1801. It can be useful in reducing the reflection of electromagnetic waves generated in each section of the sex foam 1804'. The section of the dielectric foam 1804'can be constructed, for example, as a washer made of a dielectric foam having an internal opening that supports the core 1801 in place. For purposes of illustration only, washers are referred to herein as washers 1804'. In one embodiment, the internal opening of each washer 1804'can be coaxially aligned with the axis of the core 1801. In another embodiment, the internal opening of each washer 1804'can be offset from the axis of the core 1801. In another embodiment (not shown), each washer 1804'can have a variable longitudinal thickness, as indicated by the difference in washer 1804'thickness.

In an alternative embodiment, the transmission medium 1800'' is covered with a core 1801 and a strip of dielectric foam 1804'' covered by a jacket 1806 as shown in FIG. 18K and spirally wound around the core. And can be included. Although it may not be obvious from the drawings shown in FIG. 18K, in one embodiment the strips of dielectric foam 1804'' have variable pitch (ie, i.e.) with respect to different sections of the strips of dielectric foam 1804''. , Different twist rates) can be wrapped around the core 1801. The use of variable pitch can help reduce the reflection of electromagnetic waves or other disturbances that occur between areas of core 1801 that are not covered by strips of dielectric foam 1804'. It should be further noted that the thickness (diameter) of the strip of dielectric foam 1804'' can be much larger than the diameter of the core 1801 shown in FIG. 18K (eg, more than double). ..

In one alternative embodiment, the transmission medium 1800 ″ ″ (shown in cross section) can include a non-circular core 1801 ′ covered with a dielectric foam 1804 and a jacket 1806. In one embodiment, the non-circular core 1801'can have an elliptical structure or other suitable non-circular structure as shown in FIG. 18K. In another embodiment, the non-circular core 1801'can have an asymmetric structure. The non-circular core 1801'can be used to polarize the field of electromagnetic waves induced on the non-circular core 1801'. The structure of the non-circular core 1801'can help maintain the polarization of the electromagnetic wave as it propagates along the non-circular core 1801'.

In one alternative embodiment, the transmission medium 1800'''' (shown in cross section) can include multiple cores 1801'' (only two cores are shown, but more cores). It is possible). The plurality of cores 1801 ″ can be covered with the dielectric foam 1804 and the outer cover 1806. The plurality of cores 1801 ″ can be used to polarize the field of electromagnetic waves induced on the plurality of cores 1801 ″. The structure of the plurality of cores 1801 ′ can maintain the polarization of the waveguided electromagnetic wave when the waveguided electromagnetic wave propagates along the plurality of cores 1801 ″.

It will be appreciated that the embodiment of FIG. 18K can be used to modify the embodiments of FIGS. 18G-18H. For example, the core 1842 or core 1842'can be configured to utilize the sectioned shell 1804' with gaps or one or more strips of dielectric foam 1804 ″ in between. Similarly, core 1842 or core 1842'can be configured to have a non-circular core 1801' which can have a symmetrical or asymmetric cross-sectional structure. Further, core 1842 or core 1842'can be configured to use multiple cores 1801'' in a single internal waveguide, or to use different numbers of cores if multiple internal waveguides are used. it can. Therefore, any of the embodiments shown in FIG. 18K can be applied alone or in combination with the embodiments of FIGS. 18G-18H.

Here, with reference to FIG. 18L, it is a block diagram showing a non-limiting embodiment of an example of a cohesive transmission medium that reduces crosstalk according to various aspects described herein. In one embodiment, the cohesive transmission medium 1836'can include a variable core structure 1803. By modifying the structure of core 1803, the fields of the waveguided electromagnetic waves induced in each core of the transmission medium 1836'can be sufficiently different to reduce crosstalk between cables 1838. In another embodiment, the bundling transmission medium 1836 ″ can include a variable number of cores 1803 ′ per cable 1838. By varying the number of cores 1803'per cable 1838, the field of waveguided electromagnetic waves induced in one or more cores of transmission medium 1836'' reduces crosstalk between cables 1838. Can be different enough to do. In another embodiment, the core 1803 or 1803'can be of a different material. For example, the core 1803 or 1803'can be a dielectric core 1802, an insulating conductor core 1825, a bare conductor core 1832, or any combination thereof.

It should be noted that the embodiments shown in FIGS. 18A-18D and 18F-18H may be modified by and / or in combination with some of the embodiments of FIGS. 18K and 18L. One or more of the embodiments shown in FIGS. 18K and 18L can be combined (eg, a sectioned dielectric foam 1804'or a dielectric foam with cores 1801', 1801', 1803, or 1803'. Note further (using a spiral strip of 1804''). In some embodiments, the waveguided electromagnetic waves propagating in the transmission medium 1800', 1800'', 1800''', and / or 1800'''' of FIG. 18K are the transmission medium of FIGS. 18A-18C. It can exhibit less propagation loss than the wave-guided electromagnetic waves propagating at 1800, 1820, and 1830. Further, the embodiments shown in FIGS. 18K and 18L can be configured to use the connection embodiments shown in FIGS. 18I and 18J.

Here, with reference to FIG. 18M, a block diagram showing a non-limiting embodiment of an example of a tapered stub exposed from a bundle of transmission media 1836 used as an antenna 1855 is shown. Each antenna 1855 can function as a directional antenna that radiates a wireless signal directed at a wireless communication device or guides electromagnetic wave propagation over the surface of a transmission medium (eg, power line). In one embodiment, the wireless signal emitted by antenna 1855 can be a beam steered by configuring the phase and / or other characteristics of the wireless signal generated by each antenna 1855. In one embodiment, antennas 1855 can be individually placed within the pie-pan antenna assembly to direct wireless signals in different directions.

The terms "core," "clading," "shell," and "foam" as used in this disclosure allow electromagnetic waves to remain bound to the core while propagating longitudinally along the core. It should be further noted that any type of material (or combination of materials) may be included. For example, the above-mentioned strip of dielectric foam 1804'' is a strip of ordinary dielectric material (eg, polyethylene) wound around a dielectric core 1802 (referred to herein as "wrap" for illustration purposes only). Can be replaced with. In this configuration, the average density of wraps can be small as a result of the air space between the sections of the wrap. Therefore, the effective permittivity of the wrap can be lower than the permittivity of the dielectric core 1802, which allows the waveguided electromagnetic waves to remain coupled to the core. Thus, any embodiment of the present disclosure relating to the core and the material used for the wrap around the core is another dielectric material that achieves the result of maintaining the electromagnetic waves bound to the core while propagating along the core. Can be structurally configured and / or modified using. Further, the core as described in any embodiment of the present disclosure comprises a totally or partially opaque material (eg, polyethylene) that is resistant to the propagation of electromagnetic waves having an optical operating frequency. Can be done. Therefore, the electromagnetic waves guided and coupled to the core have a non-optical frequency range (eg, less than the lowest frequency of visible light).

18N, 18O, 18P, 18Q, 18R, 18S, and 18T are non-limiting examples of waveguide devices that transmit or receive electromagnetic waves according to the various aspects described herein. It is a block diagram which shows the embodiment. In one embodiment, FIG. 18N shows a front view of a waveguide device 1865 with a plurality of slots 1863 (eg, openings or apertures) that emit electromagnetic waves with a radiated electric field (E field) 1861. In one embodiment, the radiating E-fields 1861 of a pair of symmetrically located slots 1863 (eg, slots north and south of waveguide 1865) can be directed away from each other (ie, centered on cable 1862). Radial opposite pole). Slot 1863 is shown as having a rectangle, but other shapes such as other polygons, sectors and bows, ellipses, and other shapes are possible as well. For illustration purposes only, the term north refers to the relative direction, as shown in the figure. All references in this disclosure to other directions (eg, south, east, west, and northwest, etc.) are relative to north-facing diagrams. In one embodiment, for example, in order to achieve opposite E-fields in slots 1863 in the north and south, slots 1863 in the north and south have an outer peripheral distance that is approximately one wavelength of the electromagnetic signal supplied to these slots. Can be arranged so as to have between each other. The waveguide 1865 has a cylindrical cavity in the center of the waveguide 1865, which allows the placement of the cable 1862. In one embodiment, the cable 1862 may include an insulating conductor. In another embodiment, the cable 1862 may include a non-insulated conductor. In yet another embodiment, the cable 1862 can include any embodiment of the transmission core 1852 of the cable 1850 described above.

In one embodiment, the cable 1862 can slide into the cylindrical cavity of the waveguide 1865. In another embodiment, the waveguide 1865 can utilize an assembly mechanism (not shown). An assembly mechanism (eg, a hinge or other suitable mechanism that provides a method of opening the waveguide 1865 at one or more positions) is used to place the waveguide 1865 on the outer surface of the cable 1862, or other methods. Separate pieces can be assembled together to allow the formation of the waveguide 1865 as shown. According to these and other suitable embodiments, the waveguide 1865 can be configured to be wound around the cable 1862 like a collar.

FIG. 18O shows a side view of an embodiment of the waveguide 1865. The waveguide 1865 is configured to have a hollow rectangular waveguide portion 1867 that receives the electromagnetic waves 1866 generated by the transmitter circuit, as described above in the present disclosure (see, eg, FIGS. 1 and 10A). be able to. The electromagnetic wave 1866 can be distributed in the hollow collar 1869 of the waveguide 1865 by the hollow rectangular waveguide portion 1867. The rectangular waveguide section 1867 and the hollow collar 1869 can be constructed of materials suitable for maintaining electromagnetic waves in the hollow chambers of these assemblies (eg, carbon fiber materials). Although the waveguide portion 1867 is shown and described in a hollow rectangular configuration, it should be noted that other shapes and / or other non-hollow configurations may be used. In particular, the waveguide portion 1867 can have a square or other polygonal cross section, a bow or fan cross section truncated to fit the outer surface of the cable 1862, a circular or elliptical cross section or a cross section shape. In addition, the waveguide portion 1867 may be configured as a solid dielectric material or may otherwise include a solid dielectric material.

As described above, the hollow collar 1869 can be configured to emit electromagnetic waves having opposite E-fields 1861 from each slot 1863 in a pair of symmetrically located slots 1863 and 1863'. In one embodiment, the electromagnetic waves emitted by the combination of slots 1863 and 1863'are therefore coupled to cable 1862 and propagate according to the fundamental wave mode in the absence of other wave modes-non-basic wave modes, etc. The electromagnetic wave 1868 can be induced. In this configuration, electromagnetic waves 1868 can propagate longitudinally along cable 1862 to other downstream waveguide systems coupled to cable 1862.

Since the hollow rectangular waveguide portion 1867 of FIG. 18O is closer to slot 1863 (at the north position of waveguide 1865), slot 1863 emits an electromagnetic wave having a stronger magnitude than the electromagnetic wave emitted by slot 1863'(at the south position). Note that it can occur. To reduce the size difference between these slots, slot 1863'can be made larger than slot 1863. Techniques for balancing the magnitude of signals between slots using different slot sizes are described in any of the embodiments of the present disclosure relating to FIGS. 18N, 18O, 18Q, 18S, 18U, and 18V. Applicable-some of them are described below.

In another embodiment, FIG. 18P may be configured to utilize a circuit such as a monolithic microwave integrated circuit (MMIC) 1870, each coupled to a signal input 1872 (eg, a coaxial cable providing a communication signal). The possible waveguide 1865'is shown. The signal input 1872 is generated by a transmitter circuit as described above in the present disclosure (see, eg, reference numerals 101, 1000 in FIGS. 1 and 10A), which is configured to provide an electrical signal to the MMIC 1870. be able to. Each MMIC1870 can be configured to receive a signal 1872, which can modulate the signal 1872 and use a radiating element (eg, an antenna) to radiate an electromagnetic wave having a radiation E field 1861. In one embodiment, the MMIC1870 can be configured to receive the same signal 1872 but transmit an electromagnetic wave having an E-field 1861 in the opposite direction. This can be achieved by configuring one of the MMIC1870s to transmit electromagnetic waves that are 180 degrees out of phase with the electromagnetic waves transmitted by the other MMIC1870. In one embodiment, the combination of electromagnetic waves emitted by the MMIC1870 is combined and coupled to the cable 1862, and the electromagnetic wave 1868 propagates according to the fundamental wave mode in the absence of other wave modes-non-basic wave modes, etc. Can be induced. In this configuration, electromagnetic waves 1868 can propagate longitudinally along cable 1862 to other downstream waveguide systems coupled to cable 1862.

The tapered horn 1880 can be added to the embodiments of FIGS. 18O and 18P to assist in guiding electromagnetic waves 1868 on the cable 1862, as described in FIGS. 18Q and 18R. In one embodiment in which the cable 1862 is a non-insulated conductor, the electromagnetic waves induced on the cable 1862 can have a large radial dimension (eg, 1 m). Insulation layer 1879 can be applied to a portion of cable 1862 in or near the cavity, as shown with hash lines in FIGS. 18Q and 18R, so that the smaller tapered horn 1880 can be used. The insulating layer 1879 can have a tapered end facing away from the waveguide 1865. With the added insulation, the electromagnetic wave 1868 can first be transmitted by the waveguide 1865 (or 1865') so that it is tightly coupled to the insulation, thereby reducing the radial dimension of the electromagnetic wave 1868 (eg, for example. A few cm). When the electromagnetic wave 1868 propagates away from the waveguide 1865 (1865') and reaches the tapered end of the insulating layer 1879, the radial dimension of the electromagnetic wave 1868 begins to increase, and finally the electromagnetic wave 1868 tentatively has no insulating layer. Achieve the radial dimensions that would have been had if guided on a non-insulated conductor. In the views of FIGS. 18Q and 18R, the tapered end begins at the end of the tapered horn 1880. In other embodiments, the tapered end of the insulating layer 1879 can be initiated before or after the end of the tapered horn 1880. The tapered horn may be made of metal, may be constructed of another conductive material, or may be coated or covered with a dielectric layer, or doped with a conductive material to reflect similar to a metal horn. It may be constructed of plastic or other non-conductive material that provides the properties.

In one embodiment, the cable 1862 can include any embodiment of the cable 1850 described above. In this embodiment, the waveguides 1865 and 1865'can be coupled to the transmission core 1852 of the cable 1850, as shown in FIGS. 18S and 18T. As described above, the waveguides 1865 and 1865'can guide the electromagnetic waves 1868 propagating in the inner layer of the cable 1850, in whole or in part, onto the transmission core 1852.

It should be noted that in the above embodiments of FIGS. 18Q, 18R, 18S, and 18T, the electromagnetic waves 1868 can be bidirectional. For example, electromagnetic waves 1868 of different operating frequencies can be received by slots 1863 or MMIC1870 of the waveguides 1865 and 1865', respectively. When received, the electromagnetic waves can be transmitted by a receiver circuit (see, eg, reference numerals 101, 1000 in FIGS. 1 and 10A) to generate a communication signal to be processed.

Although not shown, it should be further noted that the waveguides 1865 and 1865'may be configured to allow the electromagnetic waves 1868 to be directed upstream or downstream in the longitudinal direction. For example, a first tapered horn 1880 coupled to a first instance of waveguides 1865 or 1865'can be directed west over cable 1862, while a second instance of waveguides 1865 and 1865'. The second tapered horn 1880 coupled to can point east over the cable 1862. The first and second instances of the waveguide 1865 or 1865'provide the signal received by the first waveguide 1865 or 1865' to the second waveguide 1865 or 1865' in a repeater configuration and cable. It can be combined so that it can be retransmitted on 1862 in the eastern direction. The repeater configuration described here can also be applied over cable 1862 in the east-west direction.

The waveguide 1865 of FIGS. 18N, 18O, 18Q, and 18S can also be configured to generate an electromagnetic field having only non-basic or asymmetric wave modes. FIG. 18U shows an embodiment of a waveguide 1865 that can be configured to generate an electromagnetic field having only a non-basic wave mode. The midline 1890 represents the separation between slots where the current on the back surface (not shown) of the front plate of the waveguide 1865 changes polarity. For example, the current on the back surface of the front plate corresponding to the E field, which is radial outside (ie, pointing away from the center point of the cable 1862), is located outside the midline 1890 in some embodiments. Can be associated with slots (eg, slots 1863A and 1863B). The current on the back surface of the front plate corresponding to the E field, which is radially inside (ie, points to the center point of the cable 1862), is associated with, in some embodiments, a slot located inside the midline 1890. be able to. The direction of the current can depend, among other things, on the operating frequency of the electromagnetic wave 1866 supplied to the hollow rectangular waveguide section 1867 (see FIG. 18O).

For purposes of illustration, it is assumed that the electromagnetic wave 1866 supplied to the hollow rectangular waveguide portion 1867 has an operating frequency such that the outer peripheral distance between slots 1863A and 1863B is one perfect wavelength of the electromagnetic wave 1866. In this case, the E field of the electromagnetic waves emitted by slots 1863A and 1863B points radially outward (ie, has opposite directions). When the electromagnetic waves emitted by slots 1863A and 1863B are coupled, the resulting electromagnetic waves on the cable 1862 propagate according to the fundamental wave mode. Conversely, by repositioning one of the slots (eg, slot 1863B) inside the midline 1890 (ie, slot 1863C), slot 1863C is approximately 180 degree phased with the E field of the electromagnetic wave generated by slot 1863A. Generates an electromagnetic wave with an offset E field. As a result, the E-field orientation of the electromagnetic waves generated by the slot pairs 1863A and 1863C is substantially aligned. Thus, the coupling of electromagnetic waves emitted by slot pairs 1863A and 1863C produces an electromagnetic wave coupled to cable 1862 that propagates according to a non-basic wave mode.

To achieve a reconfigurable slot configuration, the waveguide 1865 can be configured according to the embodiment shown in FIG. 18V. Configuration (A) shows a waveguide 1865 with a plurality of symmetrically located slots. Each slot 1863 in configuration (A) can be selectively disabled by plugging the slots with a material (eg, carbon fiber or metal) to avoid the emission of electromagnetic waves. Blocked (ie, disabled) slot 1863 is shown in black, while enabled (ie, unblocked) slot 1863 is shown in white. Although not shown, the blocking material can be placed behind (or in front of) the front plate of the waveguide 1865. A mechanism (not shown) can be attached to the blocking material, which allows the blocking material to slide in and out of a particular slot 1863, much like opening and closing a window with a cover. The mechanism can be coupled to a linear motor that can be controlled by a circuit of waveguide 1865 to selectively enable or disable individual slots 1863. Using such a mechanism in each slot 1863, the waveguide 1865 can be configured to select various configurations of enabled or disabled slots 1863, as shown in the embodiment of FIG. 18V. .. Other methods or techniques of covering or opening slots (eg, the use of rotatable disks behind or in front of waveguide 1865) can also be applied to embodiments of the present disclosure.

In one embodiment, the waveguide system 1865 enables a specific slot 1863 outside the midline 1890 and disables a specific slot 1863 inside the midline 1890, as shown in configuration (B). It can be configured to generate a fundamental wave. For example, it is assumed that the outer peripheral distance between slots 1863 (ie, in the north position and south city of the waveguide system 1865) outside the midline 1890 is one wavelength. Therefore, as described above, these slots have an electric field (E field) pointing outward in the radial direction at a specific moment. Conversely, the slots inside the midline 1890 (ie, in the west and east positions of the waveguide system 1865) have a perimeter distance of 1/2 wavelength with respect to any of the slots 1863 outside the midline. Since the slots inside the midline 1890 are separated by 1/2 wavelength, such slots generate electromagnetic waves with an E field pointing outwards in the radial direction. If, instead of the west and east slots inside the midline 1890, the west and east slots 1863 outside the midline 1890 are enabled, the E-fields emitted by these slots point radially inward, which is When combined with north and south electric fields, it produces non-basic wave mode propagation. Thus, configuration (B) as shown in FIG. 18V produces electromagnetic waves with an E-field pointing radially outward in slots 1863 in the north and south, which also produces electromagnetic waves with an E-field pointing radially outward to the west. And can be used to generate in slot 1863 in the east, these electromagnetic waves, when combined, direct an electromagnetic wave with a fundamental wave mode onto the cable 1862.

In another embodiment, the waveguide system 1865 enables all north, south, west, and east slots 1863 outside the midline 1890 and all other slots 1863, as shown in configuration (C). It can be configured to be disabled. Assuming that the perimeter distances between pairs of opposing slots (eg, north and south or west and east) are separated by one perfect wavelength, configuration (C) is used to point to some radial outside. It is possible to generate an electromagnetic wave having a non-basic wave mode with an E field and other fields pointing inward in the radial direction. In yet another embodiment, the waveguide system 1865 enables northwest slot 1863 outside the midline 1890, southeast slot 1863 inside the midline 1890, and everything else, as shown in configuration (D). Slot 1863 can be configured to be disabled. Assuming that the outer perimeter distances between such slot pairs are separated by one perfect wavelength, using such a configuration, an electromagnetic wave having a non-basic wave mode with an E field aligned in the northwest direction. Can be generated.

In another embodiment, the waveguide system 1865 can be configured to generate an electromagnetic wave having a non-basic wave mode with an E field aligned in the southwest direction. This can be achieved by using a configuration different from that used in configuration (D). Configuration (E) enables southwest slot 1863 outside midline 1890, northwest slot 1863 inside midline 1890, and disables all other slots 1863, as shown in configuration (E). It can be achieved by. Assuming that the perimeter distance between pairs of such slots is separated by one perfect wavelength, using such a configuration, an electromagnetic wave having a non-basic wave mode with an E-field aligned in the southwest direction. Can be generated. Therefore, configuration (E) generates a non-basic wave mode orthogonal to the non-basic wave mode of configuration (D).

In yet another embodiment, the waveguide system 1865 can be configured to generate an electromagnetic wave having a fundamental wave mode with an E field pointing inward in the radial direction. It enables the north slot 1863 inside the midline 1890, the south slot 1863 inside the midline 1890, the east slot outside the midline 1890, and the midline, as shown in configuration (F). This can be achieved by enabling West Slot 1863 on the outside of 1890 and disabling all other Slots 1863. Assuming that the perimeter distance between the north and south slots is separated by one perfect wavelength, such a configuration is used to generate an electromagnetic wave with a fundamental wave mode with an E field inside the radius. be able to. The slots selected in configurations (B) and (F) are different, but the fundamental wave modes generated by configurations (B) and (F) are the same.

In yet another embodiment, a basic or non-basic wave mode can be generated by manipulating the E field between slots and changing the operating frequency of the electromagnetic waves 1866 supplied to the hollow rectangular waveguide portion 1867. For example, in the figure of FIG. 18U, it is assumed that at a specific operating frequency of electromagnetic wave 1866, the outer peripheral distance between slots 1863A and 1863B is one complete wavelength of electromagnetic wave 1866. In this case, the E-fields of the electromagnetic waves emitted by slots 1863A and 1863B point outward in the radial direction, as shown, and can be used in combination to guide electromagnetic waves with a fundamental wave mode onto the cable 1862. Conversely, the E-fields of the electromagnetic waves emitted by slots 1863A and 1863C are radially aligned (ie, pointing north) and used in combination to cable electromagnetic waves with non-basic wave modes, as shown. It can be guided on the 1862.

Here, it is considered that the operating frequency of the electromagnetic wave 1866 supplied to the hollow rectangular waveguide portion 1867 is changed so that the outer peripheral distance between the slots 1863A and 1863B is 1/2 wavelength of the electromagnetic wave 1866. In this case, the E-fields of the electromagnetic waves emitted by slots 1863A and 1863B are aligned in the radial direction (ie, point in the same direction). That is, the E field of the electromagnetic wave emitted by the slot 1863B points in the same direction as the E field of the electromagnetic wave emitted by the slot 1863A. Such electromagnetic waves can be used in combination to guide an electromagnetic wave having a non-basic wave mode onto the cable 1862. Conversely, the E-field of the electromagnetic waves emitted by slots 1863A and 1863C is radially outward (ie, away from the cable 1862) and used in combination to guide an electromagnetic wave with a fundamental wave mode onto the cable 1862. Can be done.

In another embodiment, the waveguide 1865'of FIGS. 18P, 18R, and 18T can also be configured to generate an electromagnetic wave having only a non-basic wave mode. This can be achieved by adding more MMIC1870, as shown in FIG. 18W. Each MMIC1870 can be configured to receive the same signal input 1872. However, the MMIC1870 can be selectively configured to emit electromagnetic waves having different phases using the controllable phase shift circuits in each MMIC1870. For example, the north and south MMIC1870 can be configured to emit electromagnetic waves with a phase difference of 180 degrees, thereby aligning the E field in either the north or south direction. Any combination of pairs of MMIC1870s (eg, MMIC1870 in the west and east, MMIC1870 in the northwest and southeast, MMIC1870 in the northeast and southwest) can be configured with E-fields facing or aligned. Therefore, the waveguide 1865'can be configured to generate an electromagnetic wave having one or more non-basic wave modes, or an electromagnetic wave having one or more fundamental wave modes, or any combination thereof.

It is proposed that slots 1863 do not need to be selected in pairs to generate electromagnetic waves with non-basic wave modes. For example, an electromagnetic wave having a non-basic wave mode can be generated by enabling a single slot from the plurality of slots shown in configuration (A) of FIG. 18V and disabling all other slots. .. Similarly, a single MMIC1870 of the MMIC1870 shown in FIG. 18W can be configured to generate electromagnetic waves with a non-basic wave mode, while all other MMIC1870s are unused, i.e. disabled. Will be done. Similarly, other wave modes and combinations of wave modes can be induced by enabling the appropriate subset of waveguide slots 1863 or other non-null MMIC1870.

The E-field arrows shown in FIGS. 18U and 18V are merely examples, and it is further proposed to represent a static diagram of the E-field. In practice, an electromagnetic wave can have a vibrating E-field that points outward at one moment and inside at another moment. For example, in a non-basic wave mode with an E field aligned in one direction (eg north), such a wave may have an E field pointing in the opposite direction (eg south) at another moment. Can be done. Similarly, a fundamental wave mode with an E-field in the radial direction can have an E-field pointing away from the cable 1862 in the radial direction at one moment and pointing away from the cable 1862 in the radial direction at another moment. .. The embodiments of FIGS. 18U-18W include electromagnetic waves having one or more non-basic wave modes, electromagnetic waves having one or more fundamental wave modes (eg, TM00 and HE11 modes), or any combination thereof. Further note that it can be configured to generate. It should be further noted that such a configuration may be used in combination with any of the embodiments described in the present disclosure. It should also be noted that the embodiments of FIGS. 18U-18W can be combined (eg, slots used in combination with MMICs).

Further note that in some embodiments, the waveguide systems 1865 and 1865'of FIGS. 18N-18W may produce a combination of fundamental and non-basic wave modes in which one wave mode is superior to the other. I want to be. For example, in one embodiment, the electromagnetic waves generated by the waveguide systems 1865 and 1865'in FIGS. 18N-18W have a weak signal component having a non-basic wave mode and a substantially strong signal component having a fundamental wave mode. Can have. Therefore, in this embodiment, the electromagnetic wave has substantially a fundamental wave mode. In another embodiment, the electromagnetic waves generated by the waveguide systems 1865 and 1865'of FIGS. 18N-18W have a weak signal component having a fundamental wave mode and a substantially strong signal component having a non-basic wave mode. Can be done. Therefore, in this embodiment, the electromagnetic wave has substantially a non-basic wave mode. Further, it is possible to generate a non-dominant wave mode that propagates only a small distance along the length of the transmission medium.

The waveguide systems 1865 and 1865'of FIGS. 18N-18W can be configured to generate instances of electromagnetic waves having wave modes that may differ from one or more generated wave modes of the coupled electromagnetic waves. Please also note. Further note that each MMIC1870 of the waveguide system 1865'of FIG. 18W can be configured to generate an instance of an electromagnetic wave having a wave characteristic different from that of another instance of the electromagnetic wave generated by another MMIC1870. I want to be. One MMIC1870 has, for example, the spatial orientation and phase, frequency, magnitude, electric field orientation and / or the spatial orientation and phase, frequency, magnitude different from the magnetic field orientation of different instances of another electromagnetic wave generated by another MMIC1870. Electromagnetic wave instances with electric and / or magnetic field orientations can be generated. Thus, the waveguide system 1865'is configured to generate instances of electromagnetic waves with different wave and spatial characteristics that, when combined, achieve the resulting electromagnetic wave with one or more desired wave modes. be able to.

From these examples, it is proposed that the waveguide systems 1865 and 1865'of FIGS. 18N-18W can be configured to generate electromagnetic waves with one or more selectable wave modes. In one embodiment, for example, the waveguide systems 1865 and 1865'from the process of selecting one or more wave modes and combining instances of electromagnetic waves with one or more configurable wave and spatial properties. It can be configured to generate an electromagnetic wave having one or more wave modes that are selected and generated. In one embodiment, for example, parametric information can be stored in a look-up table. Each entry in the lookup table can represent a selectable wave mode. The selectable wave modes can represent a single wave mode or a combination of multiple wave modes. A combination of multiple wave modes can have one or a dominant wave mode. The parametric information can provide configuration information that creates an instance of the electromagnetic wave that produces the resulting electromagnetic wave with the desired wave mode.

For example, when one or more wave modes are selected, an electromagnetic wave with the desired wave mode is achieved using parametric information from the entries associated with the selected one or more wave modes in the lookup table. Either one or more MMIC1870s can be utilized and / or their corresponding configurations can be identified. The parametric information can identify the selection of one or more MMIC1870s based on the spatial orientation of the MMIC1870 that may be required to generate an electromagnetic wave with the desired wave mode. The parametric information may or may not be the same for each of the selected MMIC1870s, so that it has a particular phase, frequency, magnitude, electric field orientation, and / or magnetic field orientation. Information can also be provided to configure each of the MMIC1870s. A look-up table with selectable wave modes and corresponding parametric information can be configured to configure the slotted waveguide system 1865.

In some embodiments, the waveguided electromagnetic waves may or may not be desirable, with the corresponding wave modes propagating over the transmission medium over a distance longer than a small distance (non-trivial distances). If it has a field intensity much higher than the other wave modes (eg, 20 dB higher), it can be considered to have the desired wave mode. Such desired one or more wave modes can be referred to as dominant wave modes and the other wave modes are referred to as non-dominant wave modes. Similarly, a wave-guided electromagnetic wave that can be said to have substantially no fundamental waveguide mode either does not have a fundamental wave mode or has a non-dominant fundamental wave mode. Waveguided electromagnetic waves that can be said to have substantially no non-basic wave mode do not have a non-basic waveguide mode or have only a non-dominant non-basic waveguide mode. In some embodiments, the wave-guided electromagnetic wave, which can be said to have only a single waveguide mode or a selected waveguide mode, can have only one corresponding dominant waveguide mode.

It should be further noted that the embodiments of FIGS. 18U-18W are applicable to the other embodiments of the present disclosure. For example, the embodiments of FIGS. 18U-18W can be used as alternative embodiments to the embodiments shown in FIGS. 18N-18T, or in combination with the embodiments shown in FIGS. 18N-18T. Can be done.

Here, with reference to FIGS. 19A and 19B, a block diagram illustrating a non-limiting embodiment of an example of a dielectric antenna and corresponding gain and field intensity plots according to the various aspects described herein. Shown. FIG. 19A shows a dielectric horn antenna 1901 having a conical structure. The dielectric horn antenna 1901 is coupled to one end 1902'of the feeder 1902 having a feed point 1902 ″ at the opposite end of the feeder 1902. The dielectric horn antenna 1901 and the feeder line 1902 (and other embodiments of the dielectric antenna described below in the present disclosure) are polyethylene materials, polyurethane materials, or other suitable dielectric materials (eg, synthetic resins, etc.). It can be constructed of a dielectric material such as plastic). The dielectric horn antenna 1901 and the feeder line 1902 (and other embodiments of the dielectric antenna described below in the present disclosure) can be configured to be substantially or totally free of any conductive material. ..

For example, the outer surface 1907 of the dielectric horn antenna 1901 and the feeder line 1902 can be non-conductive or substantially non-conductive if at least 95% of the outer surface area is non-conductive, and the dielectric horn antenna 1901 and The dielectric material used to construct the feeder 1902 may be substantially free of impurities that may be conductive (eg, less than 1 ppt, etc.) or may not impart conductivity. However, in other embodiments, it is used to couple to feed point 1902'' of feeder 1902 using one or more screws, rivets, or other coupling elements used to bond parts to each other. A limited number of conductive components such as metal connector components and / or one or more structural elements that do not significantly change the radiation pattern of the dielectric antenna can be used.

The feed point 1902 ″ can be configured to couple to the core 1852 as described above by way of illustration in FIGS. 18I and 18J. In one embodiment, the feed point 1902 ″ can be coupled to the core 1852 using a joint (not shown in FIG. 19A) such as the splice device 1860 of FIG. 18J. Other embodiments may also be used in which the feed point 1902 ″ is coupled to the core 1852. In one embodiment, the joint can be configured to contact the feed point 1902 ″ with the end point of the core 1852. In another embodiment, the joint can create a gap between the feed point 1902 ″ and the end of the core 1852. In yet another embodiment, the joint may or may not align the feed point 1902 ″ and the core 1852 coaxially or partially. Despite any combination of the above embodiments, electromagnetic waves can propagate between feedpoint 1902 ″ and core 1852 in whole or at least in part.

Cable 1850 can be coupled to the waveguide system 1865 shown in FIG. 18S or the waveguide system 1865'shown in FIG. 18T. Reference is made to the waveguide system 1865'in FIG. 18T for illustration purposes only. However, it is understood that the waveguide system 1865 of FIG. 18S or other waveguide systems may also be utilized by the following considerations. The waveguide system 1865'selects a wave mode (eg, non-basic wave mode, fundamental wave mode, hybrid wave mode, or a combination thereof as described above) and has an electromagnetic wave having a non-optical operating frequency (eg, 60 GHz). Can be configured to send an instance of. Electromagnetic waves can be directed at the interface of the cable 1850, as shown in FIG. 18T.

Instances of electromagnetic waves generated by the waveguide system 1865'can induce coupled electromagnetic waves with selected wave modes propagating from core 1852 to feedpoint 1902 ″. The coupled electromagnetic waves can propagate partially inside the core 1852 and partially on the outer surface of the core 1852. When the coupled electromagnetic wave propagates through the junction between the core 1852 and the feed point 1902 ″, it can continue to propagate partially inside the feeder line 1902 and partially on the outer surface of the feeder line 1902. In some embodiments, the portion of the coupled electromagnetic wave propagating on the outer surfaces of the core 1852 and the feeder line 1902 is small. In these embodiments, it can be said that the coupled electromagnetic waves are guided by the core 1852 and the feeder line 1902 while propagating in the longitudinal direction toward the dielectric antenna 1901 and are tightly coupled.

When the coupled electromagnetic wave reaches the proximal end of the dielectric antenna 1901 (at the junction 1902'between the feeder line 1902 and the dielectric antenna 1901), it enters the proximal end of the dielectric antenna 1901 and enters the dielectric antenna 1901. Propagates longitudinally along the axis of (shown as a hash line). By the time the coupled electromagnetic wave reaches aperture 1903, the coupled electromagnetic wave has an intensity pattern similar to that shown in the side and front views shown in FIG. 19B. The electric field intensity pattern of FIG. 19B shows that the electric field of the coupled electromagnetic wave is strongest in the central region of aperture 1903 and weaker in the outer region. In one embodiment, when the wave mode of the electromagnetic waves propagating in the dielectric antenna 1901 is the hybrid wave mode (eg HE11), the leakage of the electromagnetic waves on the outer surface 1907 is reduced, or in some cases, It disappears. Although the dielectric antenna 1901 is constructed of a solid dielectric material with no physical openings, the front or working surface of the dielectric antenna 1901 from which free space wireless signals are radiated or received may be some conventional. In technical systems, the term aperture is further referred to as the aperture 1903 of the dielectric antenna 1901, even though it may be used to describe the opening of an antenna that radiates or receives a free space wireless signal. Please note. A method of transmitting the hybrid wave mode on the cable 1850 will be considered below.

In one embodiment, the long-range antenna gain pattern shown in FIG. 19B can be extended by reducing the operating frequency of the coupled electromagnetic wave from the nominal frequency. Similarly, the gain pattern can be narrowed by increasing the operating frequency of the coupled electromagnetic wave from the nominal frequency. Therefore, the width of the beam of the wireless signal emitted by the aperture 1903 can be controlled by configuring the waveguide system 1865'to increase or decrease the operating frequency of the coupled electromagnetic waves.

The dielectric antenna 1901 of FIG. 19A can also be used to receive a wireless signal, such as a free space wireless signal transmitted by either a similar antenna or a conventional antenna design. The wireless signal received by the dielectric antenna 1901 in the aperture 1903 guides an electromagnetic wave propagating toward the feeder line 1902 into the dielectric antenna 1901. Electromagnetic waves continue to propagate from the feeder line 1902 to the junction between the feed point 1902'' and the end point of the core 1852, thereby the waveguide system 1865' coupled to the cable 1850, as shown in FIG. 18T. Will be transported to. In this configuration, the waveguide system 1865'can perform bidirectional communication using the dielectric antenna 1901. It should be further noted that in some embodiments, the core 1852 of the cable 1850 (shown by the dashed line) is configured to be co-aligned with the feed point 1902'' to avoid the curvature shown in FIG. 19A. .. In some embodiments, the co-wire configuration can reduce changes in electromagnetic propagation due to the curvature of the cable 1850.

Here, with reference to FIGS. 19C and 19D, a dielectric antenna 1901 and a corresponding gain and field strength plot coupled to or constructed integrally with the lens 1912 according to the various aspects described herein. A block diagram showing one non-limiting embodiment of an example is shown. In one embodiment, the lens 1912 can include a dielectric material having a first dielectric constant that is substantially similar to or substantially equal to the second dielectric constant of the dielectric antenna 1901. In another embodiment, the lens 1912 may include a dielectric material having a first dielectric constant different from the second dielectric constant of the dielectric antenna 1901. In any of these embodiments, the shape of the lens 1912 can be chosen or formed to equalize the delays of the various electromagnetic waves propagating at different points on the dielectric antenna 1901. In one embodiment, the lens 1912 can be an integral part of the dielectric antenna 1901, as shown in the figure above FIG. 19C, in particular the lens and the dielectric antenna 1901 are from a single dielectric material. It can be formed by molding, machining, or other methods. Alternatively, the lens 1912 can be an assembly component of the dielectric antenna 1901, as shown in the figure below FIG. 19C, and can be attached by adhesive material, brackets at the outer edge, or other suitable mounting technique. it can. The lens 1912 can have a convex structure as shown in FIG. 19C, which is configured to coordinate the propagation of electromagnetic waves in the dielectric antenna 1901. Circular lens and conical dielectric antenna configurations are shown, but other shapes include pyramidal, elliptical, and other geometries and can be implemented as well.

In particular, the curvature of the lens 1912 can be selected to reduce the phase difference between the near-field wireless signals generated by the aperture 1903 of the dielectric antenna 1901. Lens 1912 achieves this by applying a position-dependent delay to the propagating electromagnetic waves. Due to the curvature of the lens 1912, the delay varies depending on where the electromagnetic waves are emitted from the aperture 1903, eg, from electromagnetic waves propagating by the central axis 1905 of the dielectric antenna 1901, electromagnetic waves propagating radially away from the central axis 1905. Also receives a greater delay through the lens 1912. For example, an electromagnetic wave propagating towards the outer edge of aperture 1903 receives minimal or no delay through the lens. The propagation delay increases as the electromagnetic wave approaches the central axis 1905. Therefore, the curvature of the lens 1912 can be configured such that the near-field wireless signals have substantially the same phase. By reducing the phase difference of the near-field wireless signal, the width of the long-range signal generated by the dielectric antenna 1901 is narrowed, as shown by the long-range field intensity plot shown in FIG. 19D. The strength of the long-range wireless signal within the width of the main lobe increases, producing a relatively narrow beam pattern with high gain.

Here, with reference to FIGS. 19E and 19F, a dielectric antenna 1901 coupled to a lens 1912 having a ridge (or step) 1914 and a corresponding gain and field intensity plot according to the various aspects described herein. The block diagram which shows one non-limiting embodiment of an example is shown. In these figures, the lens 1912 may include the concentric ridges 1914 shown in the side and perspective views of FIG. 19E. Each ridge 1914 may include a riser 1916 and a tread 1918. The size of the tread 1918 depends on the curvature of the aperture 1903. For example, the tread 1918 at the center of aperture 1903 can be larger in size than the tread at the outer edge of aperture 1903. In order to reduce the reflection of electromagnetic waves reaching aperture 1903, each riser 1916 can be configured to have a depth that represents a wavelength selection factor. For example, the riser 1916 can be configured to have a depth of 1/4 wavelength of an electromagnetic wave propagating in the dielectric antenna 1901. Such a configuration causes the electromagnetic waves to be reflected from one riser 1916 to have a 180 degree phase difference with respect to the electromagnetic waves reflected from the adjacent risers 1916. Therefore, the out-of-phase electromagnetic waves reflected from the adjacent riser 1916 are substantially offset, thereby reducing the distortion and reflection caused by it. Although a particular riser / tread configuration is shown, other configurations with different numbers of risers, different riser shapes, etc. can be implemented as well. In some embodiments, the lens 1912 with the concentric ridges shown in FIG. 19E receives less electromagnetic reflection than the lens 1912 with the smooth convex surface shown in FIG. 19C. FIG. 19F shows a long-range gain plot resulting from the dielectric antenna 1901 of FIG. 19E.

Here, with reference to FIG. 19G, a block diagram showing a non-limiting embodiment of an example of a dielectric antenna 1901 having an elliptical structure according to various aspects described herein is shown. FIG. 19G shows a side view, a top view, and a front view of the dielectric antenna 1901. The elliptic shape is achieved by reducing the height of the dielectric antenna 1901 as indicated by reference numeral 1922 and lengthening the dielectric antenna 1901 as indicated by reference numeral 1924. The resulting elliptical 1926 is shown in the front view shown by FIG. 19G. The ellipse can be formed via machining using a forming tool or other suitable construction technique.

Here, with reference to FIG. 19H, a non-limiting embodiment of an example of a near-field signal 1928 and a long-range field signal 1930 emitted by the dielectric antenna 1901 of FIG. 19G according to the various aspects described herein. A block diagram showing a form is shown. The cross section of the near-field beam pattern 1928 mimics the ellipse of aperture 1903 of the dielectric antenna 1901. The cross section of the long-range beam pattern 1930 has a rotational offset (about 90 degrees) resulting from the ellipse of the near-field signal 1928. The offset can be identified by applying the Fourier transform to the near-field signal 1928. The cross-section of the near-field beam pattern 1928 and the cross-section of the long-range beam pattern 1930 are shown as approximately the same size to show the effect of rotation, but the actual size of the long-range beam pattern 1930 is a dielectric. It can be increased with distance from the antenna 1901.

The elongated shape of the long-range field signal 1930 and its orientation may be useful in aligning the dielectric antenna 1901 in relation to a remote receiver configured to receive the long-range field signal 1930. Can be proved. The receiver may include one or more dielectric antennas coupled to a waveguide system such as those described in the present disclosure. The long long-distance field signal 1930 can increase the probability that the remote receiver will detect the long-distance field signal 1930. In addition, the long long-range field signal 1930 has a gimbal assembly such as the dielectric antenna 1901 shown in FIG. 19M or an agent reference number 2015 named "COMMUNICATION DEVICE AND ANTENNA ASSEMBLY WITH ACTUATED GIMBAL MOUNT". Includes, but is not limited to, a co-pending application with 0603_7785-1210 and the driven gimbal mount described in US Patent Application Publication No. 14 / 873,241 filed October 2, 2015. It may be useful in situations where it is coupled to other driven antenna mounts, the contents of which are incorporated herein by reference for all purposes. In particular, the long distance field signal 1930 has only two degrees of freedom (eg, yaw and pitch are adjustable) such that the gimbal mount aligns the dielectric antenna 1901 in the direction of the receiver. , The roll is fixed) can be useful in situations where.

Although not shown, the dielectric antenna 1901 of FIGS. 19G and 19H has an integrated or attachable lens 1912, such as that shown in FIGS. 19C and 19E, to reduce the phase difference of the near field signal. It will be understood that the strength of the long-distance field signal 1930 can be increased.

Here, with reference to FIG. 19I, a block diagram of a non-limiting embodiment of an example of a dielectric antenna 1901 for adjusting a long-distance field wireless signal according to various aspects described herein is shown. In some embodiments, the width of the long-range wireless signal generated by the dielectric antenna 1901 is the number of wavelengths of electromagnetic waves propagating within the dielectric antenna 1901 that can match the surface area of the aperture 1903 of the dielectric antenna 1901. It can be said that it is inversely proportional to. Therefore, as the wavelength of the electromagnetic wave increases, the width of the long-range wireless signal increases proportionally (and its intensity decreases). In other words, as the frequency of the electromagnetic wave decreases, the width of the long-range wireless signal increases proportionally. Thus, in the direction of the receiver, the dielectric antenna with feed line 1902 to enhance the process of aligning the dielectric antenna 1901 with, for example, the gimbal assembly or other driven antenna mount shown in FIG. 19M. The frequency of the electromagnetic waves supplied to 1901 can be reduced such that the long-range wireless signal is wide enough to increase the probability that the receiver will detect a portion of the long-range wireless signal.

In some embodiments, the receiver can be configured to perform measurements on long-range wireless signals. From these measurements, the receiver can direct a waveguide system coupled to a dielectric antenna 1901 that produces a long-range wireless signal. The receiver can provide instructions to the waveguide system by means of an omnidirectional wireless signal or an interface connected between them. The instructions provided by the receiver cause the waveguide system, which controls the actuator in the gimbal assembly coupled to the dielectric antenna 1901, to adjust the orientation of the dielectric antenna 1901 to improve its alignment with the receiver. be able to. As the quality of the long-range wireless signal increases, the receiver can also instruct the waveguide system to increase the frequency of the electromagnetic waves, thereby reducing the width of the long-range wireless signal and correspondingly. Its strength increases.

In an alternative embodiment, an absorbent sheet 1932 and / or other absorbent material constructed from a carbon or conductive material is embedded in the dielectric antenna 1901, as shown by the perspective and front views shown in FIG. 19I. Can be done. When the electric field of the electromagnetic wave is parallel to the absorption sheet 1932, the electromagnetic wave is absorbed. However, in the clearance region 1934 where the absorption sheet 1932 does not exist, the electromagnetic wave propagates to the aperture 1903, thereby emitting a near field wireless signal having a width of approximately the clearance region 1934. By reducing the wavenumber relative to the surface area of the clearance region 1932, the width of the near-field wireless signal is reduced, while the width of the long-range wireless signal is increased. This property can be useful during the alignment process described above.

For example, at the start of the alignment process, the polarity of the electric field generated by the electromagnetic waves can be configured to be parallel to the absorption sheet 1932. If the remote receiver commands the waveguide system coupled to the dielectric antenna 1901 to point the dielectric antenna 1901 using an actuator of the gimbal assembly or other driven mount, the remote receiver As the signal measurements performed by the receiver improve, the waveguide system can also be instructed to incrementally adjust the alignment of the electric field of the electromagnetic waves with respect to the absorption sheet 1932. As the alignment improves, the waveguide system eventually adjusts the electric field to be orthogonal to the absorption sheet 1932. At this point, the electromagnetic waves near the absorption sheet 1932 are no longer absorbed and all or substantially all electromagnetic waves propagate to aperture 1903. Since the near-field wireless signal now covers all or substantially all of the aperture 1903, the long-field signal has a narrower width and higher intensity when directed at the receiver.

A receiver configured to receive a long-range wireless signal (as described above) utilizes a transmitter capable of transmitting a wireless signal directed at the dielectric antenna 1901 utilized by the waveguide system. It will be understood that it can also be configured to do. For purposes of illustration, such a receiver is referred to as a remote system capable of receiving long-range wireless signals and transmitting wireless signals directed to a waveguide system. In this embodiment, the waveguide system analyzes the wireless signal received by the dielectric antenna 1901, so that the quality of the wireless signal generated by the remote system improves the reception of the long-range wireless signal by the remote system. Whether to justify further adjustment to the long-range signal pattern and / or whether further alignment of the dielectric antenna with gimbals (see Figure 19M) or other driven mounts is needed. It can be configured to determine whether or not. As the reception quality of wireless signals by the waveguide system improves, the waveguide system can increase the operating frequency of electromagnetic waves, thereby reducing the width of the long-range wireless signal and correspondingly its strength. Will increase. In other modes of operation, the gimbal or other driven mount can be adjusted on a regular basis to maintain optimal alignment.

The above embodiments of FIG. 19I can also be combined. For example, a waveguide system is based on a combination of analysis of a wireless signal generated by a remote system and a message or instruction provided by the remote system indicating the quality of the long-range signal received by the remote system. Adjustments to distance field signal patterns and / or antenna orientation adjustments can be performed.

Here, with reference to FIG. 19J, a block diagram of a non-limiting embodiment of an example of a color such as a flange 1942 that can be coupled to a dielectric antenna 1901 according to various aspects described herein. Shown. The flange can be constructed of metal (eg, aluminum), dielectric material (eg, polyethylene and / or foam), or other suitable material. Flange 1942 is used to align the feed point 1902'' (and feed line 1902 in some embodiments) to the waveguide system 1948 (eg, circular waveguide), as shown in FIG. 19K. Can be done. To achieve this, the flange 1942 may include a center hole 1946 that engages the feed point 1902 ″. In one embodiment, the hole 1946 can have threading and the feeder line 1902 can have a smooth surface. In this embodiment, the flange 1942 inserts a portion of the feed point 1902'' into the hole 1946 and rotates the flange 1942 to act as a male threading machine, complementary to the soft outer surface of the feeder 1902. By forming a smooth thread, it can engage the feed point 1902'', which is constructed of a dielectric material such as polyethylene.

When the feeder 1902 is threaded by or into the flange 1942, the feed point 1902'' and the portion of the feeder 1902 extending from the flange 1942 can be shortened or lengthened by rotating the flange 1942 accordingly. .. In another embodiment, the feeder line 1902 can be pre-threaded with a mating screw that engages the flange 1942 to improve the ease of engaging the flange 1942. In yet another embodiment, the feeder line 1902 may have a smooth surface and the hole 1946 of the flange 1942 may not have threading. In this embodiment, the hole 1946 has a diameter similar to that of the feeder line 1902, and the engagement of the feeder line 1902 can be maintained in place by frictional force.

For alignment purposes, the flange 1942 can further include threaded holes 1944 with two or more alignment holes 1947, which can be used with the complementary alignment pins 1949 of the waveguide system 1948. It can be aligned, thereby assisting in aligning the hole 1944'of the waveguide system 1948 to the threaded hole 1944 of the flange 1942 (see FIGS. 19K and 19L). Once the flange 1942 is aligned with the waveguide system 1948, the flange 1942 and the waveguide system 1948 can be secured to each other using threaded screws 1950, producing the completed assembly shown in FIG. 19L. .. In the threaded design, the feed point 1902 ″ of the feeder 1902 can be adjusted inward or outward in relation to port 1945 of the waveguide system 1948 with which electromagnetic waves are exchanged. Adjustments can increase or decrease the gap 1943 between feedpoint 1902 ″ and port 1945. The adjustment can be used to adjust the coupling interface between the waveguide system 1948 and the feed point 1902 ″ of the feeder line 1902. FIG. 19L also shows that the feeder line 1902 can be used to align with the coaxially aligned dielectric foam section 1951 held by the tubular jacket 1952. The figure in FIG. 19L is similar to the transmission medium 1800 ″ shown in FIG. 18K. To complete the assembly process, the flange 1942 can be coupled to the waveguide system 1948, as shown in FIG. 19L.

Here, with reference to FIG. 19N, a block diagram of a non-limiting embodiment of an example of a dielectric antenna 1901'according to the various aspects described herein is shown. FIG. 19N shows an array of pyramidal dielectric horn antennas 1901', each with a corresponding aperture 1903'. Each antenna in the array of pyramidal dielectric horn antennas 1901'can have feeders 1902 with corresponding feed points 1902 ″ coupled to each corresponding core 1852 of a plurality of cables 1850. Each cable 1850 can be coupled to a different (or same) waveguide system 1865', such as that shown in FIG. 18T. An array of pyramidal dielectric horn antennas 1901'can be used to transmit wireless signals with multiple spatial orientations. The array of pyramidal dielectric horn antennas 1901'covering 360 degrees is such that one or more waveguide systems 1865' coupled to the antennas omnidirectional communication with other communication devices or similar types of antennas. Can be made available.

The bidirectional propagation characteristics of the electromagnetic waves described above for the dielectric array 1901 of FIG. 19A extend from the core 1852 to the feed point 1902'waveguided to the aperture 1903' of the pyramid-shaped dielectric horn antenna 1901' by the feeder line 1902. It is also applicable to electromagnetic waves propagating in the opposite direction. Similarly, the array of pyramidal dielectric horn antennas 1901'can be substantially or totally free of the conductive outer and inner conductive materials as described above. For example, in some embodiments, the array of pyramidal dielectric horn antennas 1901'and the corresponding feed points 1902' do not substantially alter the emission pattern of dielectric-only materials such as polyethylene or polyurethane materials or antennas. It can be constructed using only a small amount of conductive material.

It should be further noted that each antenna in the array of pyramidal dielectric horn antennas 1901'may have a gain and field strength map similar to that shown for the dielectric antenna 1901 in FIG. 19B. Each antenna in the array of pyramidal dielectric horn antennas 1901'can also be used to receive wireless signals for the dielectric antenna 1901 of FIG. 19A as described above. In some embodiments, a single instance of a pyramidal dielectric horn antenna can be used. Similarly, multiple instances of the dielectric antenna 1901 of FIG. 19A can be used in an array configuration similar to that shown in FIG. 19N.

Here, with reference to FIG. 19O, a block of a non-limiting embodiment of an example of an array of dielectric antennas 1901 1976 that can be configured to manipulate wireless signals according to the various aspects described herein. The figure is shown. The array of dielectric antennas 1901 1976 can be a conical antenna 1901 or a pyramidal dielectric antenna 1901'. To perform beam manipulation, the waveguide system coupled to the array 1976 of the dielectric antenna 1901 can be configured to utilize circuit 1972, which includes amplifier 1973 and phase shifter 1974, amplifier 1973 and phase shifter. Each pair of 1974 is coupled to one of the dielectric antennas 1901 in the array 1976. The waveguide system can operate a long-range wireless signal from left to right (west to east) by incrementally increasing the phase delay of the signal supplied to the dielectric antenna 1901.

For example, a waveguide system can provide a first signal to the dielectric antenna of column 1 (“C1”) that has no phase delay. The waveguide system can further provide a second signal to column 2 (“C2”), the second signal including a first signal having a first phase delay. The waveguide system can further provide a third signal to the dielectric antenna of column 3 (“C3”), the third signal including a second signal having a second phase delay. Finally, the waveguide system can provide a fourth signal to the dielectric antenna of column 4 (“C4”), which includes a third signal with a third phase delay. These phase shift signals shift the long-range wireless signal generated by the array from left to right. Similarly, long-range signals are from right to left (east to west) (from "C4" to C1), from north to south (from "R1" to "R4"), and from south to north ("R4"). To "R1"), and from southwest to northeast (from "C1-R4" to "C4-R1").

A similar technique is used to perform beam manipulation in other directions, such as southwest to northeast, by configuring the waveguide system to incrementally increase the phase of the signal transmitted by the following antenna sequence: It can also be: "C1-R4", "C1-R3 / C2-R4", "C1-R2 / C2-R3 / C3-R4", "C1-R1 / C2-R2 / C3-R3 / C4-R4" , "C2-R1 / C3-R2 / C4-R3", "C3-R1 / C4-R2", "C4-R1". Similarly, beam manipulation can be performed from northeast to southwest, northwest to southeast, southeast to northwest, and in other directions in three-dimensional space. Beam manipulation can be used, among other things, to align the array 1976 of dielectric antenna 1901 with a remote receiver and / or to direct the signal to a mobile communication device. In some embodiments, the phased array 1976 of the dielectric antenna 1901 can also be used to avoid the use of the gimbal assembly or other driven mount of FIG. 19M. Although the above described beam manipulation controlled by phase delay, similarly, gain and phase adjustment are also applied to the dielectric antenna 1901 of the phased array 1976 to provide additional control in the formation of the desired beam pattern. And can provide diversity.

Here, with reference to FIGS. 19P1 to 19P8, side block diagrams of non-limiting embodiments of cable, flange, and dielectric antenna assemblies according to the various aspects described herein are shown. FIG. 19P1 shows a cable 1850, such as those described above, including a transmission core 1852. The transmission core 1852 is a dielectric core 1802, an insulating conductor 1825, and a bare conductor 1832 shown in the transmission media 1800, 1820, 1830, 1836, 1841, and / or 1843, respectively, of FIGS. 18A-18D and 18F-18H. , Core 1842, or hollow core 1842'. The cable 1850 may further include a shell covered with a jacket (such as a dielectric shell) as shown in FIGS. 18A-18C. In some embodiments, the jacket can be conductorless (eg, polyethylene or equivalent). In other embodiments, the jacket can be a conductive shield capable of reducing leakage of electromagnetic waves propagating along the transmission core 1852.

In some embodiments, one end of the transmission core 1852 can be coupled to the flange 1942 as described above in connection with FIGS. 19J-19L. As mentioned above, the flange 1942 can allow the transmission core 1852 of the cable 1850 to be aligned with the feed point 1902 of the dielectric antenna 1901. In some embodiments, the feedpoint 1902 can be constructed of the same material as the transmission core 1852. For example, in one embodiment, the transmission core 1852 can include a dielectric core and the feed point 1902 can also include a dielectric material. In this embodiment, the dielectric constants of the transmission core 1852 and the feed point 1902 can be similar or can differ by a controlled amount. The difference in permittivity can be controlled to adjust the interface between the transmission core 1852 and the feed point 1902 for the exchange of electromagnetic waves propagating between them. In other embodiments, the transmission core 1852 may have a different structure than the feed point 1902. For example, in one embodiment, the transmission core 1852 can include an insulating conductor, while the feed point 1902 contains a dielectric material without a conductive material.

As shown in FIG. 19J, the transmission core 1852 can be coupled to the flange 1942 via the center hole 1946, but it is understood that in other embodiments such holes may be eccentric as well. Yeah. In one embodiment, the holes 1946 can have threading and the transmission core 1852 can have a smooth surface. In this embodiment, the flange 1942 serves as a die by inserting a portion of the transmission core 1852 into the hole 1946 and rotating the flange 1942 to form complementary threads on the outer surface of the transmission core 1852. , Can engage the transmission core 1852. When the flange 1942 is screwed into the transmission core 1852 or the transmission core 1852 is screwed into the flange 1942, the portion of the transmission core 1852 that extends from the flange 1942 is by rotating the flange 1942 according to the shortening or extension of that portion. It can be shortened or extended.

In another embodiment, the transmission core 1852 is pre-threaded to engage a hole 1946 in the flange 1942 to improve the ease of engagement of the flange 1942 with the transmission core 1852. be able to. In yet another embodiment, the transmission core 1852 can have a smooth surface and the holes 1946 in the flange 1942 can be screwless. In this embodiment, the hole 1946 has a diameter similar to that of the transmission core 1852, and the engagement of the transmission core 1852 can be held in place by a frictional force. It will be appreciated that there may be several other methods of engaging the transmission core 1852 with the flange 1942, including various clips, fusions, compression fittings, and the like. The feed point 1902 of the dielectric antenna 1901 can engage the other side of the hole 1946 of the flange 1942, as described for the transmission core 1852.

A gap 1943 can exist between the transmission core 1852 and the feed point 1902. However, the gap 1943 can, in one embodiment, be adjusted by rotating the feed point 1902 or vice versa while the transmission core 1852 is held in place. In some embodiments, the ends of the transmission core 1852 and feed point 1902 engaged with the flange 1942 can be adjusted to contact and thereby eliminate the gap 1943. In other embodiments, the ends of the transmission core 1852 or feed point 1902 engaged with the flange 1942 can be deliberately adjusted to provide a specified clearance size. The adjustability of the gap 1943 can provide additional degrees of freedom in adjusting the interface between the transmission core 1852 and the feed point 1902.

Although not shown in FIGS. 19P1 to 19P8, the opposite end of the transmission core 1852 of the cable 1850 is a waveguide such as that shown in FIGS. 18S and 18T, utilizing another flange 1942 and similar coupling techniques. Can be combined with the device. The waveguide device can be used to transmit and receive electromagnetic waves along the transmission core 1852. Depending on the operating parameters of the electromagnetic wave (eg, operating frequency, wave mode, etc.), the electromagnetic wave may be in the transmission core 1852, on the outer surface of the transmission core 1852, or partially in the transmission core 1852 and partially on the outer surface of the transmission core 1852. Can be propagated. When the waveguide device is configured as a transmitter, the signal generated by it propagates along the transmission core 1852 and induces electromagnetic waves transitioning to feed point 1902 at the junction between them. Next, the electromagnetic wave propagates from the feed point 1902 to the dielectric antenna 1901 and becomes a wireless signal at the aperture 1903 of the dielectric antenna 1901.

Frame 1982 is used to surround all or at least a significant portion of the outer surface of the dielectric antenna 1901 (except aperture 1903) to improve the transmission or reception of electromagnetic waves as they propagate towards aperture 1903, and / Or leakage can be reduced. In some embodiments, the portion 1984 of the frame 1982 can extend to the feed point 1902 to avoid leakage on the outer surface of the feed point 1902, as shown in FIG. 19P2. The frame 1982 can be constructed of, for example, a material that reduces the leakage of electromagnetic waves (eg, a conductive material or a carbon material). The shape of the frame 1982 can be changed based on the shape of the dielectric antenna 1901. For example, frame 1852 can have a straight surface shape with widened hem, as shown in FIGS. 19P1 to 19P4. Alternatively, the frame 1852 can have a parabolic surface shape with wide hem, as shown in FIGS. 19P5-5. It will be appreciated that frame 1852 may have other shapes as well.

Aperture 1903 can be of different shapes and sizes. In one embodiment, for example, aperture 1903 can utilize lenses having convex structures 1983 of various dimensions, as shown in FIGS. 19P1, 19P4, and 19P6 to 19P8. In other embodiments, the aperture 1903 can have a flat structure 1985 of various dimensions, as shown in FIGS. 19P2 and 19P5. In yet another embodiment, the aperture 1903 can utilize a lens having a pyramid structure 1986, as shown in FIGS. 19P3 and 19Q1. The lens of aperture 1903 can be an integral part of the dielectric antenna 1901 or can be a component coupled to the dielectric antenna 1901 as shown in FIG. 19C. Further, the lens of aperture 1903 can be constructed using the same or different material as the dielectric antenna 1901. Also, in some embodiments, the aperture 1903 of the dielectric antenna 1901 may extend out of the frame 1982, as shown in FIGS. 19P7 and 19P8, or as shown in FIGS. 19P1 to 19P6. In addition, it may be confined in the frame 1982.

In one embodiment, the permittivity of the lenses of aperture 1903 shown in FIGS. 19P1 to 19P8 can be configured to be substantially the same as or different from that of the dielectric antenna 1901. Further, one or more interiors of the dielectric antenna 1901, such as section 1986 in FIG. 19P4, may have a different dielectric constant than that of the rest of the dielectric antenna. The surface of the lens of aperture 1903 shown in FIGS. 19P1 to 19P8 may have a smooth surface, or, as described above, a ridge such as that shown in FIG. 19E to reduce surface reflection of electromagnetic waves. May have.

Depending on the shape of the dielectric antenna 1901, the frame 1982 may have different shapes and sizes, as shown in the front view shown in FIGS. 19Q1, 19Q2, and 19Q3. For example, the frame 1982 can have a pyramidal shape as shown in FIG. 19Q1. In another embodiment, the frame 1982 can have a circular shape as shown in FIG. 19Q2. In yet another embodiment, the frame 1982 can have an oval shape as shown in FIG. 19Q3.

The embodiments of FIGS. 19P1 to 19P8 and 19Q1 to 19Q3 can be combined with each other in whole or in part to create other embodiments intended by the present disclosure. Further, the embodiments of FIGS. 19P1 to 19P8 and 19Q1 to 19Q3 can be combined with other embodiments of the present disclosure. For example, the multi-antenna assembly of FIG. 20F can be configured to utilize any one of the embodiments of FIGS. 19P1 to 19P8 and 19Q1 to 19Q3. Further, a plurality of instances of the multi-antenna assembly configured to utilize one of the embodiments of FIGS. 19P1 to 19P8 and 19Q1 to 19Q3 are stacked one above the other in the same manner as the phased array of FIG. 19O. A functioning phased array can be formed. In another embodiment, as shown in FIG. 19I, an absorption sheet 1932 can be added to the dielectric antenna 1901 to control the width of the near-field and long-range signals. 19P1 to 19P8 and 19Q1 to 19Q3 and other combinations of embodiments of the present disclosure are also intended.

Here, with reference to FIGS. 20A and 20B, a block illustrating an example non-limiting embodiment of the cable 1850 of FIG. 18A used to guide electromagnetic waves waveguided over a power line supported by a utility pole. It is a figure. In one embodiment, as shown in FIG. 20A, the cable 1850 has one or more inner layers of the cable 1850 at one end, utilizing, for example, the hollow waveguide 1808 shown in FIGS. 18A-18C. It can be coupled to a microwave device that emits electromagnetic waves that are guided inside. The microwave device can transmit a signal or receive a signal from the cable 1850 using a microwave transmitter / receiver as shown in FIG. 10A. Waveguided electromagnetic waves induced in one or more inner layers of the cable 1850 propagate to the exposed stub of the cable 1850 (shown as a dotted line in FIG. 20A) located inside the horn antenna, causing the horn antenna. Electromagnetic waves can be radiated through. Therefore, the radiated signal from the horn antenna can induce a wave-guided electromagnetic wave propagating in the longitudinal direction on a power line such as a medium voltage (MV) power line. In one embodiment, the microwave device can receive AC power from a low voltage (eg 220V) power line. Alternatively, the horn antenna replaces the stub antenna as shown in FIG. 20B to induce a waveguide electromagnetic wave propagating longitudinally over a power line such as an MV power line, or one or more. Can send wireless signals to the antenna system of.

In an alternative embodiment, the hollow horn antenna shown in FIG. 20A can be replaced with a solid dielectric antenna such as the dielectric antenna 1901 of FIG. 19A or the pyramid horn antenna 1901'of FIG. 19N. In this embodiment, the horn antenna can radiate a wireless signal directed at another horn antenna, such as the bidirectional horn antenna 2040 shown in FIG. 20C. In this embodiment, each horn antenna 2040 can transmit a wireless signal to another horn antenna 2040 or receive a wireless signal from another horn antenna 2040, as shown in FIG. 20C. Such a configuration can be used to perform two-way wireless communication between the antennas. Although not shown, the horn antenna 2040 can be configured with an electromechanical device that manipulates the direction of the horn antenna 2040.

In an alternative embodiment, the first cable 1850A'and the second cable 1850B' can be coupled to the microwave device and transformer 2052, respectively, as shown in FIGS. 20A and 20B. The first cable 1850A'and the second cable 1850B' can be represented, for example, by the cables 1820 or 1830 of FIGS. 18B and 18C, respectively, where each cable has a conductive core. The first end of the conductive core of the first cable 1850A'can be coupled to a microwave device to propagate the waveguided electromagnetic waves transmitted internally. The second end of the conductive core of the first cable 1850A'is coupled to the first end of the conductive coil of the transformer 2052 to transmit the waved electromagnetic waves propagating in the first cable 1850A'. Upon receipt, the second end of the conductive coil of transformer 2052 allows the associated signal to be supplied to the first end of the second cable 1850B'. The second end of the second cable 1850B'is coupled to the horn antenna of FIG. 20A or exposed as a stub antenna of FIG. Can be induced.

Cables 1850, 1850A', and 1850B' can form a polyrod structure of antenna 1855, such as that shown in FIG. 18K, in one embodiment comprising multiple instances of transmission media 1800, 1820, and / or 1830, respectively. .. Each antenna 1855 can be coupled to, for example, a horn antenna assembly or a pie-pan antenna assembly (not shown) as shown in FIG. 20A to radiate multiple wireless signals. .. Alternatively, antenna 1855 can be used as a stub antenna in FIG. 20B. The microwave devices of FIGS. 20A and 20B can be configured to adjust the waveguided electromagnetic waves to beam-manipulate the wireless signal emitted by the antenna 1855. One or more of the antennas 1855 can also be used to guide electromagnetic waves guided over a power line.

Here, with reference to FIG. 20C, a block diagram of a non-limiting embodiment of an example of a communication network 2000 according to various aspects described herein is shown. In one embodiment, for example, the waveguide system 1602 of FIG. 16A can be incorporated into NIDs such as the network interface devices (NIDs) 2010 and 2020 of FIG. 20C. The NID with the functionality of the waveguide system 1602 can be used to enhance the transmission function between the customer premises 2002 (corporate or residential) and the pedestal 2004 (sometimes referred to as the service area interface or SAI).

In one embodiment, the central office 2030 can supply one or more fiber cables 2026 to the pedestal 2004. The fiber cable 2026 can provide high speed full duplex data service (eg, 1-100 Gbps or higher) to the mini DSLAM2024 located within the pedestal 2004. Data services can be used to transport voice, internet traffic, and media content services (eg, streaming video services, broadcast TV) and the like. In conventional systems, the mini DSLAM2024 typically includes a twisted pair telephone line (eg, an unshielded bundle of twisted pair cables such as a 24-gauge insulated solid wire surrounded by an outer insulating sheath, category 5e or Category 5e Twisted pair wires included in unshielded twisted pair (UTP) cables), and twisted pair telephone lines connect directly to customer premises 2002. In such systems, the DSL data rate tapers to 100 Mbps or less, partly due to the length of the legacy twisted pair cable pair to the customer premises 2002, among other factors.

However, the embodiment of FIG. 20C is different from the DSL system according to the prior art. In the figure of FIG. 20C, the mini DSLAM2024 comprises, for example, any cable embodiment described in connection with cables 1850 (in whole or in part, alone or in combination, FIGS. 18A-18D and 18F-18L. It can be configured to connect to the NID 2020 via (which can be represented). By using the cable 1850 between the customer premises 2002 and the pedestal 2004, the NID 2010 and 2020 can transmit and receive electromagnetic waves waveguided in uplink and downlink communications. Based on the embodiments described above, the cable 1850 is of a downlink or uplink path as long as the electric field profile of such waves in either direction is confined at least partially or entirely within the inner layer of the cable 1850. It can be exposed to rain or buried without adversely affecting electromagnetic wave propagation in either. In this example, downlink communication represents a communication path from the pedestal 2004 to the customer premises 2002, while uplink communication represents a communication path from the customer premises 2002 to the pedestal 2004. In one embodiment where the cable 1850 includes one of the embodiments of FIGS. 18G and 18H, the cable 1850 can also serve the purpose of supplying power to NID 2010 and 2020 and other equipment on the customer premises 2002 and pedestal 2004. ..

In the customer premises 2002, the DSL signal can originate from a DSL modem 2006 (which can have a built-in router and can provide wireless services such as WiFi to user equipment shown in the customer premises 2002). .. The DSL signal can be supplied to NID2010 by twisted pair telephone 2008. The NID 2010 can utilize the integrated waveguide 1602 to transmit a wave-guided electromagnetic wave 2014 directed at the pedestal 2004 on the uplink path within the cable 1850. On the downlink, the DSL signal generated by the mini DSLAM2024 can flow to NID2020 through twisted pair telephone line 2022. The waveguide system 1602 integrated with the NID 2020 can convert the DSL signal or a portion thereof from an electrical signal to a waveguide electromagnetic wave 2014 propagating in the cable 1850 on the downlink. To provide full-duplex communication, the wave-guided electromagnetic waves 2014 on the uplink operate at different carrier frequencies and / or different modulation techniques than the wave-guided electromagnetic waves 2014 on the downlink to reduce interference. Alternatively, it can be configured to avoid it. Further, on the uplink and downlink, the electromagnetic waves 2014 waveguided are waveguided by the core section of the cable 1850, as described above, and such waves are the whole or part of the waveguided electromagnetic waves. It can be configured to have a field strength profile that is confined to the inner layer of the cable 1850. Waveguided electromagnetic waves 2014 are shown outside the cable 1850, but these wave diagrams are for illustration purposes only. Therefore, the electromagnetic wave 2014 to be guided is drawn using a "hash mark" to indicate that it is guided by the inner layer of the cable 1850.

On the downlink, the NID 2010 integrated waveguide system 1602 receives the waveguided electromagnetic waves 2014 generated by the NID 2020 and again converts them into DSL signals that comply with the requirements of the DSL modem 2006. The DSL signal is then supplied to the DSL modem 2006 via a pair of twisted pairs of telephone line 2008 for processing. Similarly, on the uplink path, the NID 2020 integrated waveguide system 1602 receives the waveguide electromagnetic waves 2014 generated by the NID 2010 and again converts them into DSL signals that comply with the requirements of the mini DSLAM 2020. The DSL signal is then supplied to the mini DSLAM2024 via a pair of twisted pairs of telephone lines 2022 for processing. Due to the short length of the telephone lines 2008 and 2022, the DSL modem 2006 and mini DSLAM2024 transmit and receive DSL signals between them on the uplink and downlink at very high speeds (eg, 1 Gbps to 60 Gbps or higher). can do. Therefore, uplink and downlink can, in most situations, exceed the data rate limits of conventional DSL communication over twisted pair telephone lines.

Since downlinks typically support higher data rates than uplinks, DSL devices are typically configured for asymmetric data rates. However, cable 1850 can provide much higher speed on both down and up link roads. Firmware updates can be used to configure legacy DSL modems 2006, such as those shown in FIG. 20C, at higher speeds on both uplink and downlink. Similar firmware updates can be made to the Mini DSLAM2024 to take advantage of higher speeds on up and down links. Since the interface to the DSL modem 2006 and mini DSLAM2024 remains the traditional twisted pair telephone line, the firmware changes to perform the conversion from the DSL signal to the waveguide to the electromagnetic wave 2014 and vice versa. And besides the addition of NID 2010 and 2020, no hardware changes to the legacy DSL modem or legacy mini DSLAM are required. The use of NID allows the reuse of legacy modems 2006 and mini DSLAM2024, which can significantly reduce installation costs and system upgrades. For new buildings, an updated version of the mini DSLAM and DSL modem can be configured with an integrated waveguide system to perform the functions described above, thereby requiring NID 2010 and 2020 with an integrated waveguide system. It disappears. In this embodiment, the updated version of modem 2006 and the updated version of mini DSLAM2024 are directly connected to cable 1850 and communicate via bidirectional waveguide electromagnetic transmission, thereby twisted pair telephone lines 2008 and 2022. Eliminates the need to transmit or receive DSL signals using.

In one embodiment where the use of cable 1850 between the pedestal 2004 and the customer premises 2002 is logistically impractical or costly, the NID 2010 instead begins at the waveguide 108 on the utility pole 118 and is on the customer premises. It can be configured to connect to a cable 1850'(similar to the cable 1850 of the present disclosure) which can be buried in the soil before reaching the 2002 NID 2010. The cable 1850'can be used to receive and transmit the waveguide electromagnetic wave 2014'between the NID 2010 and the waveguide 108. The waveguide 108 can be connected via the waveguide 106, and the waveguide 106 can be coupled to the base station 104. The base station 104 can provide the data communication service to the customer premises 2002 by connecting to the central office 2030 via the fiber 2026'. Similarly, in situations where access from the central office 2030 to the pedestal 2004 is impractical via the fiber link and connection to the base station 104 is possible via the fiber link 2026', using an alternative route, the utility pole It can be connected to the NID2020 of the pedestal 2004 via a cable 1850'' (similar to the cable 1850 of the present disclosure) starting from 116. The cable 1850 ″ can also be buried before reaching NID2020.

Here, with reference to FIGS. 20D-20F, there is no limitation of an example of an antenna mount that can be used in the communication network 2000 (or other suitable communication network) of FIG. 20C according to the various aspects described herein. The block diagram of one embodiment is shown. In some embodiments, the antenna mount 2053 is provided by a dielectric power source that supplies energy to one or more waveguide systems (not shown) integrated in the antenna mount 2053 as shown in FIG. 20D. Can be coupled to medium voltage power lines. The antenna mount 2053 can include an array of dielectric antennas 1901 (eg, 16 antennas), such as those shown in the top and side views shown in FIG. 20F. The dielectric antenna 1901 shown in FIG. 20F can be of small size, as shown by a comparison of the group of dielectric antennas 1901 with a conventional ballpoint pen. In other embodiments, the utility pole mounted antenna 2054 can be used as shown in FIG. 20D. In yet another embodiment, the antenna mount 2056 can be attached to a utility pole using an arm assembly, as shown in FIG. 20E. In another embodiment, the antenna mount 2058 shown in FIG. 20E can be placed on top of a utility pole coupled to a cable 1850, such as a cable as described herein.

The array of dielectric antennas 1901 in any antenna mount of FIGS. 20D and 20E can include one or more waveguide systems as described herein with reference to FIGS. 1-20. The waveguide system can be configured to perform beam manipulation (to transmit or receive wireless signals) using an array of dielectric antennas 1901. Alternatively, each dielectric antenna 1901 can be used as a separate sector for receiving and transmitting wireless signals. In another embodiment, one or more waveguide systems integrated with the antenna mounts of FIGS. 20D and 20E combine dielectric antenna 1901 in a wide range of multi-input, multi-output (MIMO) transmit and receive techniques. It can be configured to be used. One or more waveguide systems integrated into the antenna mounts of FIGS. 20D and 20E may use any combination of dielectric antennas 1901 in any of the antenna mounts of FIGS. 20D and 20E, SISO, SIMO. Communication techniques such as MISO, SISO, and signal diversity (eg, frequency, time, space, polarization, or other form of signal diversity technique) can also be configured to apply. In yet another embodiment, the antenna mounts of FIGS. 20D and 20E can be configured with two or more stacks of the antenna arrays shown in FIG. 20F.

21A and 21B describe embodiments of downlink communication and uplink communication. The method 2100 of FIG. 21A can be initiated in step 2102, where an electrical signal (eg, a DSL signal) is generated by the DSLAM (eg, from a pedestal 2004 mini DSLAM 2020 or central office 2030) and the electrical signal is generated in step 2104. , Converted into electromagnetic waves 2014 waveguideed by NID2020, propagated on a transmission medium such as a cable 1850, and provides a downlink service to the customer premises 2002. In step 2108, the customer premises 2002 NID 2010 again converts the waveguide electromagnetic wave 2014 into an electrical signal (eg, a DSL signal), which in step 2110 is such that the DSL modem 2006 or the like via the telephone line 2008. Supplied to customer premises equipment (CPE). The electromagnetic wave 2014'that is powered and / or waveguided instead or in combination thereof is as an alternative or additional downlink (and / or uplink) path, as shown in the power system (FIG. 18G or FIG. 18H). It can be supplied to the NID 2010 from the power line 1850'(which has an internal waveguide).

In step 2122 of method 2120 of FIG. 21B, the DSL modem 2006 can supply an electrical signal (eg, a DSL signal) to the NID2010 via the telephone line 2008, and the electrical signal is the DSL signal in step 2124. It is converted into a waveguide electromagnetic wave directed to the NID 2020 by the cable 1850. In step 2128, the NID 2020 of the pedestal 2004 (or central office 2030) converts the waveguided electromagnetic wave 2014 back into an electrical signal (eg, a DSL signal), which in step 2129 is a DSLAM (eg, a mini DSLAM 2020). ) Is supplied. Instead or in combination with this, the power and waveguide electromagnetic wave 2014'as an alternative or additional uplink (and / or downlink) path, internal as shown in the power system (FIG. 18G or FIG. 18H). It can be supplied to the NID 2020 from the power line 1850'(which has a waveguide).

Here, with reference to FIG. 21C, a flow chart of a non-limiting embodiment of the method 2130 for inducing and receiving an electromagnetic wave on a transmission medium is shown. In step 2132, the waveguides 1865 and 1865'of FIGS. 18N-18T generate a first electromagnetic wave from the first communication signal (eg, supplied by a communication device such as a base station), and in step 2134. It can be configured to induce a first electromagnetic wave having a fundamental wave mode "only" at the interface of the transmission medium. In one embodiment, the interface can be the outer surface of the transmission medium, as shown in FIGS. 18Q and 18R. In another embodiment, the interface can be the inner layer of the transmission medium, as shown in FIGS. 18S and 18T. In step 2136, the waveguides 1865 and 1865'of FIGS. 18N-18T can be configured to receive a second electromagnetic wave at the interface of the same or different transmission medium described in FIG. 21C. In one embodiment, the second electromagnetic wave can have a fundamental wave mode "only". In other embodiments, the second electromagnetic wave can have a combination of wave modes such as fundamental and non-basic wave modes. In step 2138, a second communication signal can be generated from the second electromagnetic wave and processed, for example, by the same or different communication devices. The embodiments of FIGS. 21C and 21D can be applied to any of the embodiments described in the present disclosure.

Here, with reference to FIG. 21D, a flow chart of a non-limiting embodiment of the method 2140 in which an electromagnetic wave is induced and received on a transmission medium is shown. In step 2142, the waveguides 1865 and 1865'of FIGS. 18N-18W generate a first electromagnetic wave from the first communication signal (eg, supplied by the communication device), and in step 2144, the boundary of the transmission medium. It can be configured to induce a second electromagnetic wave having a non-basic wave mode "only" on the surface. In one embodiment, the interface can be the outer surface of the transmission medium, as shown in FIGS. 18Q and 18R. In another embodiment, the interface can be the inner layer of the transmission medium, as shown in FIGS. 18S and 18T. In step 2146, the waveguides 1865 and 1865'of FIGS. 18N-18W can be configured to receive electromagnetic waves at the interface of the same or different transmission media described in FIG. 21E. In one embodiment, the electromagnetic wave can have a non-basic wave mode "only". In other embodiments, the electromagnetic wave can have a combination of wave modes such as a fundamental wave mode and a non-basic wave mode. In step 2148, a second communication signal can be generated from electromagnetic waves and processed, for example, by the same or different communication devices. The embodiments of FIGS. 21E and 21F can be applied to any of the embodiments described in the present disclosure.

21E shows a flow diagram of a non-limiting embodiment of a method 2150 that radiates a signal from a dielectric antenna, such as those shown in FIGS. 19A and 19N. The method 2150 can be initiated in step 2152 and a transmitter such as the waveguide system 1865'in FIG. 18T produces a first electromagnetic wave, including a first communication signal. Therefore, in step 2153, the first electromagnetic wave induces a second electromagnetic wave on the core 1852 of the cable 1850 coupled to the feed point of any dielectric antenna described herein. The second electromagnetic wave is received at the feed point in step 2154 and propagates to the proximal end of the dielectric antenna in step 2155. In step 2156, the second electromagnetic wave continues to propagate from the proximal end of the dielectric antenna to the aperture of the antenna, thereby causing the wireless signal in step 2157, as described above in connection with FIGS. 19A-19N. Radiate.

FIG. 21F shows a flow diagram of a non-limiting embodiment of the method 2160 for receiving a wireless signal in a dielectric antenna such as the dielectric antenna of FIG. 19A or FIG. 19N. Method 2160 can be initiated in step 2161 and the dielectric antenna aperture receives the wireless signal. At step 2162, the wireless signal induces an electromagnetic wave propagating from the aperture to the feed point of the dielectric antenna. When the electromagnetic wave is received at the feed point in step 2163, it propagates to the core of the cable coupled to the feed point in step 2164. In step 2165, a receiver such as the waveguide system 1865' in FIG. 18T receives the electromagnetic wave and in step 2166 generates a second communication signal from it.

Two-way wireless communication with other dielectric antennas, such as the dielectric antenna 2040 shown in FIG. 20C, and / or portable communication devices (eg, cell phones, tablets, laptops) and buildings using methods 2150 and 2160. 19A, 19C, 19E, 19G-19I, and 19L-FIG. 19A, 19C, 19E, and 19L-FIG. 19A, 19C, 19E, and 19L-. A 19O dielectric antenna can be configured. A microwave device such as that shown in FIG. 20A can be configured with one or more cables 1850 coupled to a plurality of dielectric antennas 2040 as shown in FIG. 20C. In some embodiments, the dielectric antenna 2040 shown in FIG. 20C is configured with more dielectric antennas (eg, 19C, 19E, 19G-19I, and 19L-19O) with such antennas. The area of wireless communication can be further expanded.

Methods 2150 and 2160 are further configured to be used in conjunction with the phased array 1976 of the dielectric antenna 1901 of FIG. 19O by applying an incremental phase delay to the portion of the antenna to manipulate the emitted long-range wireless signal. can do. Methods 2150 and 2160 utilize the gimbal (which may have a controllable actuator) shown in FIG. 19M to provide a long-range wireless signal generated by the dielectric antenna 1901 and / or the orientation of the dielectric antenna 1901. Can also be configured to improve the reception of long-range wireless signals by a remote system (such as another dielectric antenna 1901 coupled to a waveguide system). In addition, methods 2150 and 2160 allow a waveguide system to receive a command, message, or wireless signal from a remote system and receive such signal by its dielectric antenna 1901 to perform long-range signal adjustment. Can be configured in.

For simplicity, each process is shown and described as a series of blocks in FIGS. 21A-21F, but the claimed subject matter is not limited by the order of the blocks and some blocks are the book. It should be understood and recognized that it may be done in a different order and / or at the same time as other blocks as shown and described in the specification. Moreover, not all of the blocks shown may be required to implement the methods described herein.

FIG. 21G shows a flow diagram of a non-limiting embodiment of a method 2170 that detects and mitigates disturbances that occur in a communication network such as the systems of FIGS. 16A and 16B. Method 2170 can be initiated in step 2172 so that network elements such as the waveguide system 1602 of FIGS. 16A and 16B monitor the degradation of the waveguided electromagnetic waves on the outer surface of the transmission medium such as power line 1610. Can be configured. The deterioration of the signal is that the magnitude of the waved electromagnetic wave signal drops below a specific magnitude threshold, the signal-to-noise ratio (SNR) drops below a specific SNR threshold, and the service quality (QoS) is 1. Below one or more thresholds, the bit error rate (BER) exceeds a specific BER threshold, the packet loss rate (PLR) exceeds a specific PLR threshold, and the ratio of reflected and transferred electromagnetic waves is specified. Signal-to-noise ratio (signal-to-noise ratio), indicating that the signal-to-noise ratio is exceeded, an unexpected change or change in wave mode, or one or more objects are causing propagation loss or scattering of the electromagnetic wave. It can be detected according to any number of factors including, but not limited to, accumulation of water on the outer surface of the transmission medium, seams of the transmission medium, broken tree branches, etc.), or any combination thereof. .. The detection device, such as the disturbance sensor 1604b of FIG. 16A, can be configured to perform one or more of the signal measurements, thereby determining whether the electromagnetic wave is subject to signal degradation. Other detection devices suitable for performing the above measurements are also contemplated by the present disclosure.

If a signal drop is detected in step 2174, the network element can proceed to step 2176 to identify and detect which one or more objects may be causing the drop. And one or more of the detected objects can be reported to the network management system 1601 of FIGS. 16A and 16B. Object detection can adversely affect spectral analysis or other forms of signal analysis, environmental analysis (eg, barometer readings, rain detection, etc.), or propagation of electromagnetic waves guided by transmission media. This can be achieved by other suitable techniques for detecting foreign matter. For example, the network element can be configured to generate spectral data derived from the electromagnetic waves received by the network element. The network element can then compare the spectral data with multiple spectral profiles stored in memory. Multiple spectral profiles can be pre-stored in the memory of the network element and, if obstacles are present on the outer surface of the transmission medium, such obstacles that may cause propagation loss or signal degradation. It can be used to characterize or identify.

For example, the accumulation of water on the outer surface of a transmission medium such as a thin layer of water and / or water droplets can be identified by a spectral profile containing spectral data modeling such obstacles, waveguideed by the transmission medium. There is a possibility that the electromagnetic wave generated may cause a signal drop. Spectral profiles are spectral data generated by test equipment (eg, waveguide systems with spectral analysis capabilities) when receiving electromagnetic waves through the outer surface of a transmission medium that has received water (eg, simulated rainfall). Can be generated in a controlled environment (such as a laboratory or other suitable test environment) by collecting and analyzing. Obstacles such as water can generate spectral signatures that differ from other obstacles (eg, seams of transmission media). Unique spectral signatures can be used to identify specific obstacles in particular. Using this technique, spectral profiles can be generated that characterize other obstacles such as tree branches and seams that have fallen into the transmission medium. In addition to the spectral profile, thresholds of different scales such as SNR, BER, and PLR can be generated. These thresholds can be selected by the service provider according to performance measurements desirable for communication networks that utilize electromagnetic waves waveguided to transport data. Some obstacles can be detected by other methods. For example, rainfall can be detected by a rain detector coupled to a network element, and a fallen tree branch can be detected by a vibration detector coupled to a network element, and so on.

If the network element does not have access to a device that detects an object that may be causing a drop in electromagnetic waves, the network element can skip step 2176 and proceed to step 2178, one or more. Notify network elements in the vicinity of (eg, one or more other waveguide systems 1602 in the vicinity of the network element) of the detected signal degradation. If the signal degradation is significant, the network element can use a different medium, such as wireless communication, for communication with nearby network elements. Alternatively, network elements substantially reduce the operating frequency of the waveguided electromagnetic waves (eg, from 40 GHz to 1 GHz), or other waveguides that operate at lower frequencies, such as control channels (eg, 1 MHz). It is possible to communicate with nearby network elements by using the generated electromagnetic waves. Low frequency control channels can be much less susceptible to interference from objects that cause signal degradation at much higher operating frequencies.

Once an alternative means of communication has been established between the network elements, in step 2180 the network elements and nearby network elements work together to coordinate the waveguided electromagnetic waves and reduce the detected signal degradation. It can be carried out. The process is a protocol that selects, for example, which of the network elements performs the adjustment of the electromagnetic wave, the frequency and magnitude of the adjustment, and the goal (eg, QoS, BER, PLR, SNR, etc.) to achieve the desired signal quality. Can be included. For example, if the object causing the signal degradation is the accumulation of water on the outer surface of the transmission medium, the network element adjusts the polarization of the electric field (E field) and / or the magnetic field of the electromagnetic wave (H field). , As shown in FIG. 21H, can be configured to maintain radial alignment of the E field. In particular, FIG. 21H is a non-limiting implementation of an example of E-field alignment of electromagnetic waves that reduces propagation loss due to the accumulation of water on a transmission medium according to the various aspects described herein. A block diagram 2101 showing a form is presented. In this example, the longitudinal cross section of the cable, such as the insulating metal cable mounting form of the transmission medium 125, is presented with a field vector indicating the E field associated with the waveguided electromagnetic waves propagating at 40 GHz. The stronger the E field, the darker the field vector is presented as compared to the weaker E field.

In one embodiment, the polarization adjustment is also known as electromagnetic waves in a particular wave mode (eg, transverse magnetic field (TM) mode, transverse electric field (TE) mode, transverse electromagnetic field (TEM) mode, or HE mode. This can be achieved by generating a hybrid of mode and TE mode). For example, the network elements include the waveguide system 1865'of FIG. 18W, and the adjustment of the polarization of the E field alternates the phase, frequency, amplitude, or combination thereof of the electromagnetic waves generated by each MMIC1870. This can be achieved by configuring one or more MMIC1870s. Certain adjustments can, for example, align the E field in the area of the water film shown in FIG. 21H perpendicular to the surface of the water. An electric field perpendicular to (or approximately perpendicular to) the surface of water induces a weaker current in the water film than an E field parallel to the water film. By inducing a weaker current, the propagation loss of the electromagnetic wave propagating in the longitudinal direction is reduced. It is also desirable to extend the density of the E field into the air above the water film. Propagation loss is also reduced when the density of the E-field in the air remains high and most of the total field strength is in the air instead of concentrating in the water and insulator regions. For example, in the E field of an electromagnetic wave tightly coupled to an insulating layer such as a goobo wave (or TM00 wave-see block diagram 2131 of FIG. 21K), the E field is perpendicular to the water film (or in the radial direction). Despite being aligned), it suffers from higher propagation loss because more of the field strength is concentrated in the water region.

Therefore, the propagation loss of an electromagnetic wave having an E field perpendicular to (or generally perpendicular to) the water film, which has a higher percentage of field strength in the air region (ie, above the water film), is the insulating layer or water. Tightly coupled electromagnetic waves with more field strength in the layer or lower than electromagnetic waves with an E field in the region of the water film causing greater loss in the direction of propagation.

FIG. 21H shows the E field in the case of the TM01 electromagnetic wave operating at 40 GHz in the longitudinal direction view of the insulating conductor. On the contrary, FIGS. 21I and 21J are cross-sectional views of the insulating conductor of FIG. 21H showing the field strength of the E field in the propagation direction of the electromagnetic wave (that is, the E field directed in the direction protruding from the pages of FIGS. 21I and 21J). 2111 and 2121 are shown respectively. The electromagnetic waves shown in FIGS. 21I and 21J have TM01 wave modes at 45 GHz and 40 GHz, respectively. FIG. 21I shows that the intensity of the E field in the propagation direction of the electromagnetic wave is high in the region between the outer surface of the insulator and the outer surface of the water film (that is, the region of the water film). High intensity is indicated by a bright color (the brighter the color, the stronger the intensity of the E field directed toward the page popping out). FIG. 21I shows that there is a high density E-field polarized longitudinally within the region of the water film, which produces a high current in the water film and thus a high propagation loss. Therefore, under certain circumstances, electromagnetic waves at 45 GHz (having TM01 wave mode) are less suitable for mitigating rainwater or other obstacles placed on the outer surface of the insulating conductor.

On the contrary, FIG. 21J shows that the intensity of the E field in the propagation direction of the electromagnetic wave is weaker in the water film region. The weaker intensities are indicated by a darker color in the area of the water film. The lower intensities are the result of the E-field being polarized approximately perpendicular or radial to the water film. The radialally aligned E-fields are also densely present in the air region, as shown in FIG. 21H. Therefore, an electromagnetic wave at 40 GHz (having a TM01 wave mode) creates an E field that induces a lower current into the water film than a 45 GHz wave having the same wave mode. Therefore, the electromagnetic wave of FIG. 21J exhibits more suitable properties for reducing propagation loss due to the accumulation of water films or water droplets on the outer surface of the insulating conductor.

In the first iteration of step 2182, FIG. 21H shows that the physical properties of the transmission medium can vary and the effects of water or other obstacles on the outer surface of the transmission medium can result in non-linear effects. It is not always possible to precisely model all situations to achieve the shown E-field polarization and E-field concentration in the air. To speed up the mitigation process, the network element can be configured to select a starting point for adjusting the electromagnetic waves from the look-up table in step 2186. In one embodiment, a look-up table entry can be searched for a match with the type of object detected in step 2176 (eg, rainwater). In another embodiment, a look-up table can be searched for a match with spectral data derived from the affected electromagnetic waves received by the network element. The table entry provides specific parameters (eg, frequency, phase, amplitude, wave mode, etc.) that adjust the electromagnetic wave to achieve at least coarse adjustments that achieve similar E-field characteristics as shown in FIG. 21H. be able to. Coarse adjustments can function to improve the probability of converging on a solution that achieves the desired propagation characteristics described above in relation to FIGS. 21H and 21J.

Once the coarse adjustments have been made in step 2186, the network element can determine in step 2184 whether the adjustments have improved the signal quality to the desired target. Step 2184 can be carried out by coordinating and exchanging network elements. For example, in step 2186, it is considered that the network element generates an electromagnetic wave adjusted according to the parameters obtained from the lookup table and transmits the adjusted electromagnetic wave to a nearby network element. At step 2184, the network element is tuned by receiving feedback from nearby network elements that have received the tuned electromagnetic wave, analyzing the quality of the received wave according to an agreed target target, and providing the results to the network element. Can determine if the signal quality has improved. Similarly, the network element can test the tuned electromagnetic waves received from the nearby network element and provide feedback containing the results of the analysis to the nearby network element. Although specific search algorithms have been described above, other search algorithms such as gradient search, genetic algorithm, global search, or other optimization techniques can be utilized as well. Therefore, steps 2182, 2186, and 2184 represent the tuning and testing process performed by the network element and its neighbors.

With this in mind, in step 2184, the network element (or network element in its vicinity) does not achieve the desired parameter target (eg, SNR, BER, PLR, etc.) with one or more signal qualities. If determined, in step 2182 an incremental adjustment can be initiated for the network element and its neighbors. In step 2182, the network element (and / or its neighbors) has a target target. Until achieved, it can be configured to incrementally adjust the magnitude, phase, frequency, wave mode, and / or other adjustable features of the electromagnetic wave. To perform these adjustments, the network. The waveguide system 1865'of FIG. 18W can be configured in the element (and its neighboring network elements). The network element (and its neighboring network elements) utilizes two or more MMIC1870s to generate electromagnetic waves. One or more operating parameters can be incrementally adjusted to achieve signal-to-noise ratios polarized in a particular direction (eg, away from the propagation direction in the region of the water film). Two or more MMIC1870s. Can also be configured to incrementally adjust one or more operating parameters of an electromagnetic wave that achieves an E-field with a high density in the air region (outside the obstacle).

The iterative process can be a trial-and-error process in which network elements are coordinated to reduce the time it takes to converge on a solution that improves upstream and downstream communication. As part of the coordination process, for example, one network element can be configured to adjust the magnitude of the electromagnetic waves but not the wave mode, while another network element adjusts the wave mode, It can be configured so that the size is not adjusted. According to experiments and / or simulations, the service provider may establish a combination of iterations and adjustments in the electromagnetic wave that achieves the desired properties in the electromagnetic wave to reduce obstacles to the outer surface of the transmission medium and program it into the network element. it can.

In step 2184, when the network element detects that the signal quality of the upstream and downstream electromagnetic waves has been improved to the desired level to achieve one or more parametric targets (eg, SNR, BER, PLR, etc.). , The network element can proceed to step 2188 and resume communication according to the tuned upstream and downstream electromagnetic waves. During the communication in step 2188, the network element may be configured to transmit upstream and downstream test signals based on the original electromagnetic wave to determine if the signal quality of such waves has improved. it can. These test signals can be transmitted at regular intervals (eg, once every 30 seconds or at other suitable cycles). Each network element may, for example, analyze the spectral data of the received test signal to determine if the desired spectral profile and / or other parametric target (eg, SNR, BER, PLR, etc.) is achieved. Can be done. If the signal quality is not improved or is negligible, the network element can be configured in step 2188 to continue communication using the tuned upstream and downstream electromagnetic waves.

However, if the signal quality is improved enough to return to the use of the original electromagnetic wave, the network element proceeds to step 2192 and is set to generate the original electromagnetic wave (eg, original wave mode, original magnitude, original). Frequency, original phase, original spatial orientation, etc.) can be restored. Signal quality can be improved as a result of removing obstacles (eg, evaporation of rainwater, removal of fallen tree branches by field personnel, etc.). At step 2194, the network element can utilize the original electromagnetic waves to initiate communication and perform upstream and downstream tests. In step 2196, if the test performed in step 2194 determines by the network element that the signal quality of the original electromagnetic wave is satisfactory, the network element resumes communication with the original electromagnetic wave. As mentioned above, it is possible to proceed to step 2172 and subsequent steps.

Pass / fail of the test can be determined by analyzing the test signal in step 2196 according to the parametric target associated with the original electromagnetic wave (eg, BER, SNR, PLR, etc.). If the test performed in step 2194 is determined to fail in step 2196, the network element can proceed to steps 2182, 2186, and 2184 as described above. Since the previous adjustments to the upstream and downstream electromagnetic waves may have already been determined to pass, the network element can restore the settings used for the previously adjusted electromagnetic waves. Therefore, one iteration of any one of steps 2182, 2186, and 2184 may be sufficient to return to step 2188.

In some embodiments, restoration of the original electromagnetic wave may be desirable, for example, if the data throughput with the original electromagnetic wave is better than the data throughput with the tuned electromagnetic wave. Please note. However, if the adjusted electromagnetic data throughput is better than or substantially closer to the original electromagnetic data throughput, the network element can instead be configured to continue from step 2188.

21H and 21K describe the TM01 wave mode, but other wave modes (eg HE wave, TE wave, TEM wave, etc.) or a combination of wave modes can achieve the desired effect shown in FIG. 21H. Please also note that. Thus, the wave mode alone or in combination with one or more other wave modes produces an electromagnetic wave having an E-field characteristic that reduces propagation loss, as described in connection with FIGS. 21H and 21J. be able to. Therefore, such a wave mode is intended as a possible wave mode that can be configured to be generated by network elements.

It should be further noted that method 2170 may be configured in step 2182 or 2186 to generate other wave modes that may not be subject to cutoff frequencies. For example, FIG. 21L shows block diagram 2141 of a non-limiting embodiment of an example of a hybrid wave electric field according to the various aspects described herein. A wave with HE mode has a linearly polarized E field pointing away from the direction of electromagnetic wave propagation and is perpendicular (or approximately perpendicular) to the region of an obstacle (eg, the water film shown in FIGS. 21H-21J). Can be. Waves with HE mode can be configured to generate an E-field that extends substantially outward of the outer surface of the insulating conductor so that more of the total storage field intensity is in the air. Therefore, some electromagnetic waves having the HE mode can exhibit the characteristics of a large wave mode having an E field orthogonal to or substantially orthogonal to the region of the obstacle. As mentioned above, such properties can reduce propagation loss. Electromagnetic waves with HE mode also have unique characteristics that do not have cutoff frequency (ie, can operate at quasi-DC), unlike other wave modes that have nonzero cutoff frequency.

Here, with reference to FIG. 21M, a block diagram 2151 showing an example non-limiting embodiment of the electric field characteristics of a hybrid wave vs. a goobo wave according to the various aspects described herein is shown. FIG. 2158 shows the energy distribution between the HE11 mode wave and the goobo wave of the insulating conductor. The energy plot of FIG. 2158 assumes that the amount of power used to generate the Goobo wave is the same as the HE11 wave (ie, the area under the energy curve is the same). In the figure of FIG. 2158, the Goobo wave has a sharp drop in power when extending beyond the outer surface of the insulating conductor, while the HE11 wave has a substantially low drop in power beyond the insulating layer. Therefore, the Goobo wave has a higher energy density near the insulating layer than the HE11 wave. FIG. 2167 shows a similar goobo and HE11 energy curve when the water film is present on the outer surface of the insulator. The difference between the energy curves of FIGS. 2158 and 2167 is that the power drop of the Goubo and HE11 energy curves begins at the outer edge of the insulator in the case of FIG. 2158 and at the outer edge of the water film in the case of FIG. 2167. is there. However, the energy curves 2158 and 2167 show the same behavior. That is, the electric field of the Goubo wave is tightly coupled to the insulating layer, and when exposed to water, causes a larger propagation loss than the electric field of the HE11 wave, which has a higher density outside the insulating layer and the water film. These characteristics are shown in FIG. 2168 of HE11 and FIG. 2159 of Goobo, respectively.

By adjusting the operating frequency of the HE11 wave, the E field of the HE11 wave has a larger storage field strength in the area in the air when compared with the insulator and the field in the water layer surrounding the outside of the insulator. Block of 21N As shown in FIG. 2169, it can be configured to extend substantially upward of a thin water film. FIG. 21N shows an electric wire having an insulation radius of 1.5 cm with a radius of 1 cm and a dielectric constant of 2.25. As the operating frequency of the HE11 wave decreases, the E field extends outward, increasing the size of the wave mode. At a particular operating frequency (eg, 3 GHz), the expansion of the wave mode can be substantially larger than the diameter of the insulated wire and any obstacles that can be present on the insulated wire.

The HE11 wave has a lower propagation loss than the Goobo wave when the transmission medium is exposed to water or other obstacles by having an E field perpendicular to the water film and placing most of its energy outside the water film. .. The Goobo wave has the desired radial E-field, but the wave is tightly coupled to the insulating layer, creating a dense E-field in the area of the obstacle. Therefore, when an obstacle such as a water film is present on the outer surface of the insulating conductor, the goobo wave still suffers a high propagation loss.

Here, with reference to FIGS. 22A and 22B, a block diagram showing a non-limiting embodiment of an example of a waveguide system 2200 that delivers hybrid waves according to the various aspects described herein is shown. The waveguide system 2200 may include a probe 2202 coupled to a slidable or rotatable mechanism 2204 that allows the probe 2202 to be placed in a different position or orientation with respect to the outer surface of the insulating conductor 2208. Mechanism 2204 may include a coaxial feed 2206 or other coupling that allows the transmission of electromagnetic waves by probe 2202. The coaxial feed 2206 can be located on the mechanism 2204 such that the path difference between the probes 2202 is 1/2 of the wavelength or some odd integer multiple of the wavelength. When the probe 2202 produces an electromagnetic signal of opposite phase, the electromagnetic wave can be guided on the outer surface of the insulating conductor 2208 having a hybrid mode (HE11 mode or the like).

Mechanism 2204 can also be coupled to a motor or other actuator (not shown) that moves probe 2202 to the desired position. In one embodiment, for example, the waveguide system 2200 rotates the probe 2202 to different positions (eg, left and west) (assuming the probe 2202 is rotatable) and blocks FIG. 2300 of FIG. It may include a controller instructing the motor to generate an electromagnetic wave having a horizontally polarized HE11 mode as shown in. To guide the electromagnetic waves over the outer surface of the insulating conductor 2208, the waveguide system 2200 may further include a tapered horn 2210 shown in FIG. 22B. The tapered horn 2210 can be aligned coaxially with the insulating conductor 2208. An additional insulating layer (not shown) can be placed on the insulating conductor 2208 to reduce the cross-sectional dimensions of the tapered horn 2210. The additional insulating layer can be similar to the tapered insulating layer 1879 shown in FIGS. 18Q and 18R. The additional insulating layer can have a tapered end pointing away from the tapered horn 2210. The tapered insulating layer 1879 can reduce the size of the initial electromagnetic wave transmitted according to the HE11 mode. As the electromagnetic wave propagates towards the tapered end of the insulating layer, the HE11 mode expands until it reaches full size as shown in FIG. In other embodiments, the waveguide system 2200 may not need to use the tapered insulating layer 1879.

FIG. 23 shows that HE11 mode waves can be used to reduce obstacles such as rainwater. For example, as shown in FIG. 23, it is considered that the water film surrounds the outer surface of the insulating conductor 2208 due to rainwater. Further, it is assumed that water droplets have collected under the insulating conductor 2208. As shown in FIG. 23, the water film occupies a small portion of the total HE11 wave. Also, by having the horizontally polarized HE11 waves, the water droplets are in the area with the lowest density of the HE11 waves, reducing the loss caused by the water droplets. Therefore, the HE11 wave is tightly coupled to the Goubo wave or the insulating conductor 2208 and therefore suffers much lower propagation loss than a wave having a mode with more energy in the area occupied by water.

It is proposed that the waveguide system 2200 of FIGS. 22A and 22B can be replaced by other waveguide systems of the present disclosure capable of generating electromagnetic waves having HE mode. For example, the waveguide system 1865'of FIG. 18W can be configured to generate electromagnetic waves with HE mode. In one embodiment, the two or more MMIC1870s of the waveguide system 1865'can be configured to generate anti-phase electromagnetic waves to generate a polarized E field, such as being in HE mode. In another embodiment, different pairs of MMIC1870s are selected to polarize HE waves at different spatial locations (eg, north and south, west and east, northwest and southeast, northeast and southeast, or other subfraction combinations). Can be generated. Further, the waveguide system of FIGS. 18N-18W may be configured to deliver electromagnetic waves having HE mode onto core 1852 of one or more embodiments of cable 1850 suitable for propagating HE mode waves. it can.

The HE wave can have desirable properties for reducing obstacles on the transmission medium, but certain wave modes with cutoff frequencies (eg, TE mode, TM mode, TEM mode, or a combination thereof) are also sufficient. It is proposed that it can be used to reduce the propagation loss caused by obstacles by exhibiting waves with a large, polarized E field that is orthogonal (or approximately orthogonal) to the obstacle region. Method 2070 can be configured to generate such a wave mode from a look-up table, for example, in step 2086. For example, a wave mode with a cutoff frequency that is larger than an obstacle and has a polarized E field that is perpendicular (or approximately perpendicular) to the obstacle can be determined by experiment and / or simulation. Once the combination of parameters (eg, magnitude, phase, frequency, wave mode, spatial position, etc.) that generate one or more waves with a cutoff frequency with low propagation loss characteristics is determined, the parametric result of each wave Can be stored in a lookup table in the memory of the waveguide system. Similarly, wave modes with cutoff frequencies that exhibit reduced propagation loss can be iteratively generated by any of the search algorithms described above in the process of steps 2082-2084.

For simplicity, each process is shown and described as a series of blocks in FIG. 21G, but the claims are not limited by the order of the blocks and some blocks are shown herein. Understand and recognize that it can be done in a different order and / or at the same time as other blocks as described. Moreover, not all the blocks shown are required to implement the methods described herein.

FIG. 24 shows a flow chart of a non-limiting embodiment of the method 2400 for transmitting and receiving electromagnetic waves. Method 2400 can be configured for the waveguide 2522 shown in FIGS. 25A-25C. Method 2400 can be initiated in step 2402 where the generator produces a first electromagnetic wave. In step 2404, the waveguide guides the first electromagnetic wave to the interface of the transmission medium, thereby guiding the second electromagnetic wave to the interface of the transmission medium in step 2406. Steps 2402 to 2406 can be applied to the waveguide 2522 of FIGS. 25A, 25B, and 25C. The generator can be MMIC1870 or slot 1863, as shown in FIGS. 18N-18W. For purposes of illustration only, it is assumed that the generator is an MMIC 2524 located within the waveguide 2522, as shown in FIGS. 25A-25C. 25A to 25C show longitudinal directions of the cylindrical waveguide 2522, but the waveguide 2522 may have other structural shapes (eg, square, rectangular, etc.).

Referring to the figure of FIG. 25A, the waveguide 2522 covers the first region 2506 of the core 2528. Within the first region 2506, the waveguide 2522 has an outer surface 2522A and an inner surface 2523. The inner surface 2523 of the waveguide 2522 reflects an electromagnetic wave, thereby allowing the waveguide 2522 to be configured to guide the first electromagnetic wave 2502 towards the core 2528 in step 2404. Or it can be constructed from other materials. The core 2528 may include a dielectric core (as described herein) that extends to the inner surface 2523 of the waveguide 2522. In other embodiments, the dielectric core can be enclosed by cladding (such as shown in FIG. 18A), which extends the cladding to the inner surface 2523 of the waveguide 2522. In yet another embodiment, the core 2528 may include an insulating conductor, in which case the insulator extends to the inner surface 2523 of the waveguide 2522. In this embodiment, the insulating conductor can be a power line, coaxial cable, or other type of insulating conductor.

In the first region 2506, the core 2528 includes an interface 2526 that receives the first electromagnetic wave 2502. In one embodiment, the interface 2526 of the core 2528 can be configured to reduce the reflection of the first electromagnetic wave 2502. In one embodiment, the interface 2526 has a tapered structure that can reduce the reflection of the first electromagnetic wave 2502 from the surface of the core 2528. Other structures can be used for the interface 2526. For example, interface 2526 can be partially tapered and rounded at the tip. Therefore, any structure, configuration, or conforming interface 2526 capable of reducing the reflection of the first electromagnetic wave 2502 is contemplated by the present disclosure. In step 2406, the first electromagnetic wave 2502 induces (or otherwise generates) a second electromagnetic wave 2504 propagating within the core 2528 in the first region 2506 covered by the waveguide 2522. The inner surface 2523 of the waveguide 2522 traps the second electromagnetic wave 2504 in the core 2528.

The second region 2508 of the core 2528 is not covered by the waveguide 2522, thereby exposing it to the environment (eg, air). In the second region 2508, the second electromagnetic wave 2504 starts at the discontinuity between the edge of the waveguide 2522 and the exposed core 2528 and extends outward. In order to reduce the radiation from the second electromagnetic wave 2504 to the environment, the core 2528 can be configured to have a tapered structure 2520. As the second electromagnetic wave 2504 propagates along the tapered structure 2520, the second electromagnetic wave 2504 remains substantially coupled to the tapered structure 2520, thereby reducing radiation loss. The tapered structure 2520 ends at the transition from the second region 2508 to the third region 2510. In the third region, the core has a cylindrical structure 2529 having a diameter equal to the end point of the tapered structure 2520 at the junction between the second region 2508 and the third region 2510. In the third region 2510 of the core 2528, the second electromagnetic wave 2504 suffers a low propagation loss. In one embodiment, this can be achieved by choosing the diameter of the core 2528 that allows the second electromagnetic wave 2504 to loosely couple with the outer surface of the core 2528 in the third region 2510. Alternatively or in combination thereof, the propagation loss of the second electromagnetic wave 2504 is reduced by configuring the MMIC 2524 to adjust the wave mode, wavelength, operating frequency, or other operating parameters of the first electromagnetic wave 2502. be able to.

FIG. 25D shows a portion of the waveguide 2522 of FIG. 25A, which is shown as a cylindrical ring (not showing the MMIC 2524 or tapered structure 2526 of FIG. 25A). In the simulation, the first electromagnetic wave is injected at the end point of core 2528 shown in FIG. 25D. In the simulation, it is assumed that there is no such reflection, based on the assumption that the tapered structure 2526 (or other suitable structure) is used to reduce the reflection of the first electromagnetic wave. The simulation is shown as two vertical cross-sectional views of the core 2528 and a cross-sectional view of the core 2528 partially covered by the waveguide section 2523A. In the case of a vertical cross-sectional view, one of the figures is a photograph-like view of a part of the first figure.

As can be seen from the simulation, the electromagnetic field 2532 of the second electromagnetic wave 2504 is confined within the core 2528 by the inner surface 2523 of the waveguide section 2523A. When the second electromagnetic wave 2504 enters the second region 2508 (no longer covered by the waveguide section 2523A), the tapered structure 2520 extends over the tapered outer surface of the core 2528, thus reducing the radiation loss of the electromagnetic wave field 2532. To do. When the second electromagnetic wave 2504 enters the third region 2510, the electromagnetic wave field 2532 stabilizes and then remains loosely coupled to the core 2528 (shown in vertical and cross-sectional views), thereby reducing propagation loss. To do.

FIG. 25B provides an alternative embodiment for the tapered structure 2520 in the second region 2508. The tapered structure 2520 extends the waveguide 2522 into a second region 2508 having the tapered structure 2522B, and as shown in FIG. 25B, the first region 2506, the second region 2508, and the third region 2508 of the core 2528. This can be avoided by maintaining the diameter of the core 2528 throughout region 2510. The horn structure 2522B can be used to reduce the radiation loss of the second electromagnetic wave 2504 when the second electromagnetic wave 2504 transitions from the first region 2506 to the second region 2508. In the third region 2510, the core 2528 is exposed to the environment. As described above, the core 2528 is configured to reduce the propagation loss due to the second electromagnetic wave 2504 in the third region 2510. In one embodiment, this can be achieved by choosing the diameter of the core 2528 that allows the second electromagnetic wave 2504 to be loosely coupled to the outer surface of the core 2528 in the third region 2510. Alternatively or in combination, the propagation loss of the second electromagnetic wave 2504 can be reduced by adjusting the wave mode, wavelength, operating frequency, or other performance parameters of the first electromagnetic wave 2502.

The waveguide 2522 of FIGS. 25A and 25B can also be configured to receive electromagnetic waves. For example, the waveguide 2522 of FIG. 25A can be configured to receive electromagnetic waves in step 2412. This can be represented by the electromagnetic wave 2504 propagating from east to west in the third region 2510 (in the orientation shown in the lower right of FIGS. 25A and 25B) towards the second region 2508. Upon reaching the second region 2508, the electromagnetic wave 2504 gradually becomes tightly coupled to the tapered structure 2520. When the electromagnetic wave 2504 reaches the boundary between the second region 2508 and the first region 2506 (that is, the edge of the waveguide 2522), it propagates in the core 2528 confined by the inner surface 2523 of the waveguide 2522. .. Eventually, the electromagnetic wave 2504 reaches the end point of the tapered interface 2526 of the core 2528 and is radiated as a new electromagnetic wave 2502 waveguideed by the inner surface 2523 of the waveguide 2522.

One or more antennas of the MMIC2524 are configured to receive the electromagnetic wave 2502, thereby converting the electromagnetic wave 2502 into an electrical signal that can be processed by a processing device (eg, receiver circuit and microprocessor) in step 2414. can do. To avoid interference between the electromagnetic waves transmitted by the MMIC 2524, the remote waveguide system transmitting the electromagnetic wave 2504 received by the electromagnetic wave 2522 of FIG. 25A has different operating frequencies, different wave modes, different phases, or other adjustments. It can be configured to transmit electromagnetic waves 2504 with possible operating parameters to avoid interference. The electromagnetic wave can be received by the waveguide 2522 of FIG. 25B in the same manner as described above.

Here, referring to FIG. 25C, the waveguide 2522 of FIG. 25B can be configured to support a transmission medium 2528 having no end point, such as that shown in FIG. 25C. In this example, the waveguide 2522 includes a chamber 2525 in the first region 2506 of the core 2528. The chamber 2525 creates a gap 2527 between the outer surface 2521 of the core 2528 and the inner surface 2523 of the waveguide 2522. The gap 2527 provides ample room for placing the MMIC 2524 on the inner surface 2523 of the waveguide 2522. Symmetric regions: 2508 and 2508', 2510 and 2510', and 2512 and 2512' can be configured in the waveguide 2522 so that the waveguide 2522 can receive electromagnetic waves from any direction. In the first region 2506, the chamber 2525 of the waveguide 2522 has two tapered structures 2522B'and 2522B'. These tapered structures 2522B'and 2522B'' allow electromagnetic waves to gradually enter or exit chamber 2525 from either direction of core 2528. A directional antenna can be configured on the MMIC 2524 to emit a first electromagnetic wave 2502 directed east to west or west to east in relation to the longitudinal view of the core 2528. Similarly, the directional antenna of the MMIC2524 can be configured to receive longitudinally propagating electromagnetic waves on the core 2528 from east to west or west to east. The process of transmitting electromagnetic waves is similar to that described for FIG. 25B, depending on whether the directional antenna of the MMIC2524 is transmitting from east to west or from west to east.

Although not shown, the waveguide 2522 in FIG. 25C can be configured with one or more hinges or other mechanisms that allow the waveguide 2522 to be split into two separable portions. This mechanism can be used to allow the installation of the waveguide 2522 on the core 2528 without end points. Other mechanisms for installing the waveguide 2522 of FIG. 25C on the core 2528 are also intended by the present disclosure. For example, the waveguide 2522 can be configured with a slot opening extending in the longitudinal direction throughout the waveguide structure. In the slot-designed waveguide 2522, the regions 2522C'and 2522C of the waveguide 2522 can be configured such that the inner surface 2523 of the waveguide 2522 is tightly coupled to the outer surface of the core 2528. The tight coupling between the inner surface 2523 of the waveguide 2522 and the outer surface of the core 2528 prevents the waveguide 2522 from sliding or moving with respect to the core 2528. The tight coupling in regions 2522C'and 2522C can also be applied to the hinge design of waveguide 2522.

The waveguide 2522 shown in FIGS. 25A, 25B, and 25C can be configured to perform one or more embodiments described in the other figures of the present disclosure. Therefore, it is intended that such an embodiment is applicable to the waveguide 2522 of FIGS. 25A, 25B, and 25C. Further, any configuration of the core in the present disclosure can be applied to the waveguide 2522 of FIGS. 25A, 25B, and 25C.

For brevity, each process is shown and described as a series of blocks in FIG. 24, but the claims are not limited by the order of the blocks and some blocks are described herein. Understand and recognize that it can be performed in a different order than shown and described in and / or at the same time as other blocks. Moreover, not all of the blocks shown are required to carry out the methods described herein.

Others described and shown in the waveguide transmitters 2522 and / or the drawings of the present disclosure (eg, FIGS. 7-14, 18N-18W, 22A, 22B, and other drawings) of FIGS. 25A-25D. On a transmission medium having an outer surface made of, for example, a dielectric material (eg, an insulator, oxidation, or other material having dielectric properties), the waveguide transmitter of the above, and any method thereof, the outer surface of the transmission medium. A single wave mode or wave mode that reduces propagation loss when propagating through a substance such as a liquid placed above (eg, water produced by moisture, snow, dew, sleet, and / or rain). It should be further noted that it can be configured to produce a combination of.

25E, 25F, 25G, 25H, 25I, 25J, 25K, 25L, 25M, 25N, 25O, 25P, 25Q, 25R, 25S, and 25T. FIG. 3 is a block diagram showing a non-limiting embodiment of an example of a wave mode (and associated electric field plots) that can be generated on the outer surface of a transmission medium by one or more of the waveguides of the present disclosure and their adaptation. .. First, with reference to FIG. 25E, a diagram showing a longitudinal cross section of the transmission medium 2542 is provided. The transmission medium 2542 is a conductor 2543, a dielectric material 2544 (eg, insulator, oxidation, etc.) disposed on the conductor 2543, and a substance / water film 2545 (or water, or water) disposed on the outer surface of the dielectric material 2544. Can include liquids, or other accumulations of other substances). The transmission medium 2542 can be exposed to (or can be placed in vacuum) a gaseous substance such as air or air 2546. The thicknesses of the conductor 2543, the dielectric material 2544, and the water film 2545 are not drawn to a constant scale and are therefore merely exemplary. Although not shown in FIG. 25E, the conductor 2543 can be a cylindrical conductor surrounded by a dielectric material 2544 and air 2546, such as a single conductor, twisted multiple strands, and the like. For simplification of the illustrations of the present disclosure, only the portion of conductor 2543 near the top (or first) surface is shown. Furthermore, symmetrical portions of the dielectric material 2544, the water film 2545, and the air 2546 arranged below the conductor 2543 (or opposite / lower side of the conductor 2543) in the longitudinal cross section of FIG. 25E are not shown.

In certain embodiments, gravity can concentrate the water film 2545 primarily on a limited portion of the outer surface of the transmission medium 2542 (eg, below the transmission medium 2542). Therefore, in this example, it is not necessary to completely surround the outer surface of the dielectric material with the water film 2545. It should be further noted that the water film 2545 can be a water droplet or a ball of water rather than a continuous water film. FIG. 25E shows an insulating conductor (ie, a conductor 2543 surrounded by a dielectric material 2544), eg, bare wires or other wires of various structural shapes (eg, cylindrical, rectangular, square, etc.). A transmission medium 2542 having another configuration, such as a transmission medium 2542 composed only of a non-insulating conductor or a dielectric material, is also possible and is applicable to the present disclosure.

FIG. 25E is delivered onto the outer surface of the transmission medium 2542 by one of the waveguide transmitters described in the present disclosure or its adaptation and travels longitudinally along the transmission medium 2542 corresponding to the indicated wave propagation direction. The electric field of the basic transverse magnetic wave mode in the form of the TM00 wave mode, which is sometimes called the goobo wave mode, is further shown. The electromagnetic waves propagating along the transmission medium via the transverse magnetic (TM) mode extend radially outward from the transmission medium and are a function of the radial low field component orthogonal to the longitudinal direction and the propagation distance parallel to the time and longitudinal directions. It has both a longitudinal z-field component that changes as, but has an electric field that does not have an azimuth phi component that is orthogonal to both the longitudinal and radial directions.

The TM00 Goobo wave mode produces an electric field with a significant radial low field component extending away from the conductor with high field strength throughout the dielectric in region 2550. The TM00 Goubo wave mode also produces an electric field with a prominent radial low field component extending into the conductor with high field strength throughout the dielectric in region 2550 ″. Further, in the region 2550'between the regions 2550 and 2550 ″, an electric field is generated that is smaller in magnitude and has a significant longitudinal z-field component. The presence of these electric fields inside the dielectric causes some attenuation, but the loss in these regions is negligible compared to the effects of thin water films as described below.

An enlarged view of a small area of the transmission medium 2542 (indicated by the dashed oval) 2548 is shown in the lower right of FIG. 25E. The enlarged view 2548 shows the electric field existing in a small region of the transmission medium 2542 at a higher resolution. The enlarged view shows the electric field, the water film 2545, and the air 2546 in the dielectric material 2544. Most of the electric field shown in region 2547 of enlarged view 2548 has a large longitudinal component, especially in the region near the outer surface of the dielectric material 2544 in the area of water film 2545. When the electromagnetic wave indicating the TM00 (Goobo) wave mode propagates in the longitudinal direction (left to right or right to left), the area of the high vertical component of the electric field shown in region 2547 makes the electric field larger than the water film 2545. The portions are traversed, thereby producing a large propagation loss, which can be attenuation on the order of 200 dB / M, for example, for frequencies in the range of 24 GHz to 40 GHz.

FIG. 25F shows a simulated electromagnetic wave having a TM00 wave mode and the case where such a wave propagates over a dry transmission medium 2542 implemented as a 1 m (length) insulating conductor and a wet transmission medium 2542. A vertical cross-sectional view of the effect when propagating above is shown. For illustration purposes only, the simulation assumes a lossless insulator to focus on an analysis of the degree of attenuation caused by the 0.1 mm water film. As illustrated, when an electromagnetic wave with a TM00 wave mode propagates over a dry transmission medium 2452, the wave suffers minimal propagation loss. In contrast, when the same electromagnetic wave with TM00 (Goobo) wave mode propagates through a damp transmission medium 2542, for example at frequencies in the range of 24 GHz to 40 GHz, the attenuation is 200 dB over a length of 1 m of the insulating conductor. Incurs a large propagation loss that exceeds.

FIG. 25G shows a simulation showing the magnitude and frequency characteristics of an electromagnetic wave with TM00 Goubo wave mode when propagating on a dry insulating conductor 2542 and when propagating on a damp insulating conductor 2542. For illustration purposes only, the simulation assumes a lossless insulator to focus on an analysis of the degree of attenuation caused by the 0.1 mm water film. The plot shows that when the transmission medium 2542 is damp, an electromagnetic wave with TM00 Goubo wave mode is attenuated by about 200 dB / M over a frequency range of 24 GHz to 40 GHz. In contrast, the plot for the dry insulating conductor 2542 is largely undamped at frequencies in the same range.

25H and 25I show electric field plots of electromagnetic waves with TM00 Goubo wave modes having operating frequencies of 3.5 GHz and 10 GHz, respectively. The vertical axis represents the field strength rather than the distance, but the hash lines are superimposed on the plots of FIGS. 25H and 25I (as well as the plots of FIGS. 25M-25S), and the conductor, insulation with respect to the position indicated by the x-axis. Shows each part of the body and water film. The field strength was calculated in FIGS. 25H and 25I (as well as the plots in FIGS. 25M-25S) based on the absence of water, but nevertheless the plot shown in FIG. 25H is dielectric. The presence of water at the indicated locations on the outer surface of the body material 2544 aids in explaining why the TM00 Goobo wave mode at low frequencies has low propagation loss.

In order to understand the plots of FIGS. 25H and 25I, it is important to understand the difference between the radial low field and the longitudinal z field. When looking at the longitudinal section of the transmission medium 2542, such as shown in FIG. 25E, the low field passes through the dielectric material 2544, the possible aqueous film 2545, and the air 2546 and is radially outward or radial inward from the conductor 2543. Represents an electric field extending in (perpendicular to the longitudinal axis). In contrast, the z-field is an electric field aligned with the dielectric material 2544, the water film 2545, or the air 2546 so as to be parallel to the longitudinal axis of the transmission medium 2542. A propagating electromagnetic wave having only an electric field component that is radial or orthogonal to the water film 2545 propagates longitudinally (left to right or right to left) along the outer surface of the transmission medium 2542. At that time, it does not receive a large attenuation of the field strength. In contrast, a propagating electromagnetic wave having an electric field component parallel (or longitudinal) to the water film 2545, that is, a z-field aligned with the water film 2545, having a field intensity substantially greater than zero. When the electromagnetic wave propagates in the longitudinal direction (left to right or right to left) along the outer surface of the transmission medium 2542, it receives a large loss of field strength (that is, propagation loss).

In the case of the TM00 goobo wave mode at 3.5 GHz shown in the plot of FIG. 25H, as shown in FIG. 25H, the z-field component of the electric field starts from the outer surface of the dielectric material 2544 and is where the water film 2545 can be. Through, it has a field strength smaller than that of the low field (radial) component. In particular, plot 25H shows the magnitude of the field intensities of the low and z field components at the peak, as a function of the radial distance away from the center of the transmission medium. The field strength was calculated based on the absence of water, but nevertheless, the plot shown in FIG. 25G shows the low frequency when water is present at the indicated location on the outer surface of the dielectric material 2544. It is helpful to explain why the TM00 goobo wave mode in TM00 has a low propagation loss. In practice, according to one embodiment, the electric field has a large radial component (eg, radial low field) orthogonal to the propagation direction, and conversely has a relatively small longitudinal component (eg, z field) as the material /. When it is provided in the region of the water film, the propagation loss can be relatively low. Thus, electromagnetic waves with TM00 Goobo wave mode at 3.5 GHz have a water film 2545 placed on the outer surface of the dielectric material 2544 (due to rain, snow, dew, sleet, and / or excessive moisture). If not subject to large attenuation. However, this is not true for all frequencies, especially as frequencies approach the millimeter wave range.

For example, FIG. 25I shows a plot of TM00 wave mode at 10 GHz. In this plot, the field intensities of the z-field component in the water film region are relatively large when compared to the low-field (radial) component. Therefore, the propagation loss is very high. FIG. 25J shows that when a water film having a thickness of 0.1 mm is present on the outer surface of the insulating conductor, the TM00 wave mode at 4 GHz is much lower than the TM00 wave mode at 10 GHz, which exhibits an attenuation of 45 dB / M. It is shown to be attenuated by 62 dB / M. Therefore, the TM00 wave mode operating at high frequencies approaching the millimeter wave frequency can suffer large propagation loss when the water film is present on the outer surface of the transmission medium.

Here, with reference to FIG. 25K, an example showing an electromagnetic wave having a TM01 wave mode (for example, a non-basic wave mode) propagating on the outer surface of the dielectric material 2544 is provided. In the enlarged view 2548, the region 2547 is a region where the electric field of the electromagnetic wave having the TM01 wave mode is close to the outer surface of the dielectric material 2544 in the area of the water film 2545, and the large radial low field component and the not so large longitudinal z field component. Indicates that it has. The TM01 wave mode has a cutoff frequency greater than zero hertz. When composed of the waveguide transmitters of the present disclosure (its adaptations or other transmitters) such that electromagnetic waves with TM01 wave mode operate in a frequency range near the cutoff frequency, the low power portion is the dielectric material 2544. On the other hand, most of the electric power is concentrated in the air 2546.

The TM01 wave mode, in region 2551, mainly causes the radial low field component to extend away from the conductor and reverse in the dielectric 2544, creating an electric field pointing inward from the air into the dielectric 2544 on the surface of the dielectric. .. In the TM01 wave mode, in region 2551'', the radial low field component mainly extends into the conductor, the radial low field component is reversed in the dielectric 2544, and on the surface of the dielectric outside the dielectric 2544 into the air. It also generates an electric field that points to. Further, in the region 2551'between the regions 2551 and 2551 ″, an electric field mainly having a longitudinal z-field component is generated in the dielectric layer 2544. As in TM00 mode, the presence of these electric fields inside the dielectric 2544 causes some attenuation, but the losses in these regions are large enough to prevent the propagation of TM01 waves over long distances. It may not be.

Further, the electric field in the TM01 wave mode in the region 2547 of the water film 2545 is mainly a radial component and a relatively small longitudinal component. Therefore, the propagating wave does not suffer a large propagation loss when the electromagnetic wave having this field structure propagates in the longitudinal direction (left to right or right to left) along the outer surface of the transmission medium 2542.

FIG. 25L is a vertical cross-sectional view of an electromagnetic wave having a TM01 wave mode, where such waves propagate over a dry transmission medium 2542 and at a frequency slightly lower than the millimeter wave frequency and in a damp transmission medium. The effect when propagating on 2542 is shown. As shown in the figure, when an electromagnetic wave having a TM01 wave mode propagates on a dry transmission medium 2542, the propagation loss suffered by the wave is minimal. When an electromagnetic wave with TM01 wave mode propagates over a damp transmission medium 2542, in contrast to an electromagnetic wave with TM00 Goobo wave mode at similar frequencies, the electromagnetic wave with TM01 wave mode has only a small additional attenuation. receive. Thus, for example, an electromagnetic wave having a TM01 wave mode in the millimeter frequency range is much less susceptible to an increase in propagation loss due to the presence of the water film 2545 than an electromagnetic wave having a TM00 Goobo wave mode in the same frequency range.

FIG. 25M provides an electric field plot of the radial low field component and the longitudinal z field component of the TM01 wave mode electric field having an operating frequency at 30.437 GHz, which is 50 MHz above the cutoff frequency. The cutoff frequency is 30.387 GHz based on a radius of 4 mm for the conductor 2543 and a thickness of 4 mm for the dielectric material 2544. Higher or lower cutoff frequencies are possible with the TM01 wave mode when the dimensions of the conductor 2543 and the dielectric material 2544 differ from this example. In particular, the plot shows the magnitude of the field intensities of the low and z field components at the peak, as a function of the radial distance away from the center of the transmission medium. The field intensities were calculated based on the absence of water, but nevertheless, the plot shown in FIG. 25M shows the TM01 wave when water is present at the indicated location on the outer surface of the dielectric material 2544. Help explain why the mode has low propagation loss. As described above, the electric field substantially orthogonal to the water film 2545 does not suffer a large loss of field strength, while the electric field parallel / longitudinal to the outer surface of the dielectric material 2544 in the area of the water film 2545 is this. When an electromagnetic wave having a field structure propagates along a transmission medium 2542, it suffers a large loss of field strength.

In the TM01 wave mode, the longitudinal z-field component of the electric field begins at the outer surface of the dielectric material 2544 and, through the water film 2545, has a very small field strength compared to the size of the radial field, as shown in FIG. 25M. Can have. Therefore, electromagnetic waves with TM01 wave mode at 30.437 GHz will occur if the water film 2545 is placed on the outer surface of the dielectric material 2544 (due to rain, dew, snow, sleet, and / or excessive moisture). At frequencies above 6 GHz (eg at 10 GHz-see Figure 25J), it undergoes much less attenuation than TM00 Goobo wave mode.

FIG. 25N shows a plot showing the magnitude and frequency characteristics of an electromagnetic wave with TM01 wave mode when propagating over a dry transmission medium 2542 and when propagating over a damp transmission medium 2542. The plot shows that when the transmission medium 2542 is damp, the electromagnetic waves having the TM01 wave mode receive less attenuation when the TM01 wave mode is operating in the frequency range near the cutoff frequency (eg, 28 GHz to 31 GHz). .. In contrast, the TM00 Goobo wave mode undergoes a large attenuation of 200 dB / M over the same frequency range, as shown in the plot of FIG. 25G. Therefore, the plot of FIG. 25N supports the results of the dry and wet simulations shown in FIG. 25L.

25O, 25P, 25Q, 25R, and 25S show other wave modes that can exhibit similar characteristics to those shown in TM01 wave mode. For example, FIG. 25O provides an electric field plot of the radial low field component and the longitudinal z field component of the TM02 wave mode electric field having an operating frequency at 61.121 GHz, which is 50 MHz above the cutoff frequency. As mentioned above, the cutoff frequency can be higher or lower if the dimensions of the conductor 2543 and the dielectric material 2544 are different from this example. In particular, the plot shows the magnitude of the field intensities of the low and z field components at the peak, as a function of the radial distance away from the center of the transmission medium. The field strength was calculated based on the absence of water, but as shown in FIG. 25O, the z-field component of the electric field would start from the outer surface of the dielectric material 2544 and be occupied by the water film 2545. Throughout the position, it can have a very small field strength relative to the size of the radial row field. Therefore, the electromagnetic wave exhibiting the TM02 wave mode is attenuated much less than the wave mode having a much larger longitudinal z-field component at the position corresponding to the water film due to the accumulation of water on the outer surface of the dielectric layer. Receive.

FIG. 25P is an electric field plot of the radial low field component, the longitudinal z field component, and the azimuth phi field component of the EH11 wave mode electric field having an operating frequency at 31.153 GHz, which is above the cutoff frequency of 50 MHz. Illustration is provided. As before, the cutoff frequency in the example of FIG. 25P can be higher or lower depending on the dimensions of the conductor 2543 and the dielectric material 2544.

Non-TM wave modes, such as the hybrid EH wave mode, are azimuthal fields that are orthogonal to the radial low field component and the longitudinal z field component and tangentially surround the transmission medium 2542 in clockwise and / or counterclockwise directions. Ingredients can be included. Like the z-field component, the phi-field (azimuth) component on the outer surface of the dielectric 2544 can also cause large propagation losses in the presence of the thin film 2545 of water. The plot of FIG. 25P shows the magnitude of the field intensities of the low field component, the phi field component, and the z field component at the peak as a function of the radial distance away from the center of the transmission medium 2542. The field intensities were calculated based on the absence of water, but the z-field and phi-field components of the electric field each start from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545. It has a very small field strength relative to the size of the radial field. Therefore, an electromagnetic wave having an EH11 wave mode is more than a wave mode having a much larger longitudinal z-field component and a phi field component at a position corresponding to the water film due to the accumulation of water on the outer surface of the dielectric layer. Receives much less attenuation.

FIG. 25Q shows the radial low field component, the longitudinal z field component, and the azimuth phi field of the electric field in the higher order hybrid wave mode, especially the EH12 wave mode having an operating frequency at 61.5 GHz, which is 50 MHz above the cutoff frequency. A diagram of an electric field plot of the components is provided. As before, the cutoff frequency can be higher or lower depending on the dimensions of the conductor 2543 and the dielectric material 2544. In particular, the plot shows the magnitude of the field intensities of the low, phi, and z field components at the peak, as a function of the radial distance away from the center of the transmission medium. The field intensities were calculated based on the absence of water, but the z-field and phi-field components of the electric field each start from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545. It has a very small field strength relative to the size of the radial field. Therefore, an electromagnetic wave having an EH12 wave mode has a much larger longitudinal z-field component and a phi-field component at a position corresponding to the water film due to the accumulation of water on the outer surface of the dielectric layer than the wave mode. Receives much less attenuation.

FIG. 25R is an electric field plot of the radial low field component, the longitudinal z field component, and the azimuth phi field component of the HE22 wave mode electric field having an operating frequency at 36.281 GHz, which is above the cutoff frequency of 50 MHz. Illustration is provided. As before, the cutoff frequency can be higher or lower depending on the dimensions of the conductor 2543 and the dielectric material 2544. In particular, the plot shows the magnitude of the field intensities of the low, phi, and z field components at the peak, as a function of the radial distance away from the center of the transmission medium. The field intensities were calculated based on the absence of water, but the z-field and phi-field components of the electric field each start from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545. It has a small field strength relative to the size of the radial field. Therefore, the electromagnetic wave exhibiting the EH22 wave mode is more than the wave mode having a much larger longitudinal z-field component and a phi-field component at the position corresponding to the water film due to the accumulation of water on the outer surface of the dielectric layer. Receives much less attenuation.

FIG. 25S shows the radial low field component, the longitudinal z field component, and the azimuth phi field of the electric field in the higher order hybrid wave mode, especially the HE23 wave mode having an operating frequency at 64.425 GHz, which is 50 MHz above the cutoff frequency. A diagram of an electric field plot of the components is provided. As before, the cutoff frequency can be higher or lower depending on the dimensions of the conductor 2543 and the dielectric material 2544. In particular, the plot shows the magnitude of the field intensities of the low, phi, and z field components at the peak, as a function of the radial distance away from the center of the transmission medium. The field intensities were calculated based on the absence of water, but the z-field and phi-field components of the electric field each start from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545. It has a small field strength relative to the size of the radial field. Therefore, the electromagnetic wave exhibiting the HE23 wave mode is more than the wave mode having a much larger longitudinal z-field component and a phi-field component at the position corresponding to the water film due to the accumulation of water on the outer surface of the dielectric layer. Receives much less attenuation.

Based on the observations of the electric field plots of FIGS. 25M and 25O, the electromagnetic wave having the TM0m wave mode, m> 0, is a much larger longitudinal z-field component and / at the position corresponding to the water film. Alternatively, it can be said that it receives less propagation loss than the wave mode having a phi field component. Similarly, based on the observations of the electric field plots of FIGS. 25P and 25Q, the electromagnetic wave having the EH1m wave mode, m> 0, is a much larger longitudinal z-field at the position corresponding to the water film. It can be said that it receives less propagation loss than the wave mode having components and / or phi field components. Further, based on the observations of the electric field plots of FIGS. 25R and 25S, the electromagnetic wave having the HE2m wave mode, m> 1, is a much larger longitudinal z-field component at the position corresponding to the water film. And / or it can be said that it receives less propagation loss than the wave mode having a phi field component.

Others described and shown in the waveguide transmitters 2522 and / or the drawings of the present disclosure (eg, FIGS. 7-14, 18N-18W, 22A-22B and other drawings) of FIGS. 25A-25D. The waveguide transmitter is in TM0m wave mode or EH1m wave mode (here) on a transmission medium having an outer surface made of, for example, a dielectric material (eg, an insulator, oxidation, or other material having dielectric properties). , M> 0), HE2m wave mode (where m> 1), or when the z-field component (and azimuth field component) is present in the proximal region above the outer surface of the transmission medium in which the water film can be present. It should be further noted that can be configured to generate or induce electromagnetic waves with any other type of wave mode that exhibits low field intensity in the azimuth field component). Since the particular wave mode has an electric field structure near the outer surface of the transmission medium that is less susceptible to propagation loss, the waveguide transmitters of the present disclosure are placed on the outer surface of the transmission medium alone or in combination, if appropriate. In addition, when propagating through a substance such as a liquid (eg, water produced by moisture and / or rain), it can be configured to generate an electromagnetic wave having the above-mentioned wave mode characteristics that reduces propagation loss. It should be further noted that in certain embodiments, the transmission medium used for the propagation of one or more of the wave modes may consist solely of a dielectric material.

It should also be noted that with reference to the TM01 wave mode of FIG. 25K again, the region 2549 in enlarged FIG. Certain electric field vectors in region 2549 will appear to have longitudinal field components located within the water film 2545, but such vectors have very low field intensities and region 2547 (region 2549). The quantity is considerably lower, even when compared to the higher intensity radial field components placed within). Nevertheless, a small number of electric field vectors with non-zero longitudinal components in region 2549 can be a contributor to the small attenuation described above in relation to the wet transmission medium 2542 of FIG. 25L. The adverse effect of the electric field vector in the small Eddie region 2549 of FIG. 25K has a much higher field intensity and a considerable number of electric fields with large longitudinal components in the TM00 Goobo wave mode region 2547 of FIG. 25E within the water film 2545. Much less than the negative effects caused by the vector. As mentioned above, the electric field vector in region 2547 of TM00 Goobo wave mode propagates much higher at frequencies above 6 GHz, as shown by the wet transmission medium 2542 in FIGS. 25F, 25G, 25I, and 25J. It causes a loss (attenuation of as much as 200 dB / M), which is not the case in the TM01 wave mode.

It should also be noted that the electric field diagrams of FIGS. 25E and 25K are not static in time and space. That is, when an electromagnetic wave propagates in space in the longitudinal direction along a transmission medium, the electric field associated with the electromagnetic wave changes as time progresses when viewed at a static position of the transmission medium. Thus, the electric field plots shown in FIGS. 25H, 25I, 25M, and 25O-25S are non-static, can be scaled and contracted, and can be reversed in polarity as well. The electric field plot is not static, but the z-field component (and azimuth field component) in the cases of TM0m wave mode and EH1m wave mode (here, m> 0) and HE2m wave mode (here, m> 1) The mean field intensity of the azimuth field component (if present) is much lower than the mean field intensity indicated by the z field component of TM00 Goobo wave mode above 6 GHz. Therefore, the TM0m wave mode, the EH1m wave mode (here, m> 0) and the HE2m wave mode (here, m> 1) are more than the TM00 goobo wave mode in the frequency range exceeding 6 GHz in the presence of the water film 2545. Also suffers much lower propagation loss.

It should be further noted that the electric field of TM00 Goobo wave mode is substantially different from TM0m wave mode and EH1m wave mode (here m> 0) and HE2m wave mode (here m> 1). For example, consider the electric fields of TM00 Goobo wave mode and TM01 wave mode shown in the cross-sectional view of the transmission medium 2542 shown in FIG. 25T. The TM00 Goobo wave mode exhibits a radial electric field that extends away from the conductor with high field strength throughout the dielectric. This behavior is shown in region 2550 of FIG. 25E at some point in time and space of transmission medium 2542. In contrast, the TM01 wave mode extends away from the conductor, substantially reducing the field strength at the midpoint of the dielectric, reversing the polarity towards the outer surface of the dielectric and increasing the field strength. Indicates an electric field. This behavior is shown in region 2551 of FIG. 25K at some point in time and space of transmission medium 2542.

In TM00 Goubo wave mode, if the cross-section slices shown in FIG. 25T remain the same over time, the electric field in region 2550'(in FIG. 25E) eventually reaches the cross-section slices that reduce the field intensity and the region When the electric field at 2550'' reaches the cross-section slice, the polarity is suddenly reversed. In contrast, in TM01 wave mode, the electric field in region 2551'(in FIG. 25K) eventually reaches a cross-section slice that is longitudinal (ie, points out of the drawing in FIG. 25T), thereby. The electric field shown in FIG. 25T is generated, the TM01 wave mode appears to have disappeared, and then when the electric field in region 2551'' reaches the cross-section slice, it reverses its polarity from that shown in FIG. 25T and returns.

The electromagnetic wave modes described in FIGS. 25E-25T and other sections of the present disclosure can be transmitted on the outer surface alone or in a combination of multiple wave modes in whole or in part, or are described herein. It will be appreciated that it can be embedded in any one of the transmission media (eg, FIGS. 18A-18L). These electromagnetic modes can be converted into wireless signals by any antenna described in the present disclosure (eg, FIGS. 18M, 19A-19F, 20A-20F), or wireless signals received by the antennas. Therefore, it should be further noted that it can be converted again into one or more electromagnetic wave modes propagating along one of the transmission media. The methods and systems described in the present disclosure can also be applied to these electromagnetic modes for transmission, reception, or processing of these electromagnetic modes, or for adaptation or modification of these electromagnetic modes. Any waveguide transmitter (or its adaptation) transmits one or more electromagnetic waves with a target field structure or target wave mode indicating spatial alignment of the electric field to reduce propagation loss and / or signal interference. It should be further noted that it can be configured to induce or generate on the medium. The waveguide device of FIG. 25U provides a non-limiting example of the suitability of the waveguide transmitters of the present disclosure.

Here, with reference to FIG. 25U, a non-limiting embodiment of an example of a waveguide device 2522 according to the various aspects described herein is shown. The waveguide device 2522 is similar to the waveguide device 2522 shown in FIG. 25C and has a small number of fits. In the illustration of FIG. 25U, the waveguide device 2522 is coupled to a transmission medium 2542 that includes a conductor 2543 and an insulating layer 2543 that together form an insulating conductor such as that shown in the drawings of FIGS. 25E and 25K. Although not shown, the waveguide device 2522 can be constructed with two halves, the two halves connected together at one end in the longitudinal direction using one or more mechanical hinges. , The longitudinal edge can be opened at the opposite end of one or more hinges to place the waveguide device 2522 on the transmission medium 2542. Once arranged, the waveguide device 2522 can be secured to the transmission medium 2542 using one or more latches at the longitudinal edge facing the one or more hinges. Other embodiments that couple the waveguide device 2522 to the transmission medium 2542 can also be used and are therefore intended by the present disclosure.

The chamber 2525 of the waveguide device 2522 of FIG. 25U contains a dielectric material 2544'. The dielectric material 2544'in the chamber 2525 can have a dielectric constant similar to that of the dielectric layer 2544 of the insulating conductor. Further, for transmitting or receiving electromagnetic waves, a disk 2525'with a central hole 2525' can be used to divide the chamber 2525 into two halves. The disk 2525'can be constructed of a material (eg, carbon, metal, or other reflective material) that does not allow electromagnetic waves to travel between the halves of the chamber 2525. The MMIC2524'can be placed inside the dielectric material 2544' of the chamber 2525, as shown in FIG. 25U. Further, the MMIC 2524'can be arranged near the outer surface of the dielectric layer 2543 of the transmission medium 2542. FIG. 25U shows the MMIC2524'including an antenna 2524B'(monopole antenna, dipole antenna, or other antenna, etc.) that can be configured to be longitudinally aligned with the outer surface of the dielectric layer 2543 of the transmission medium 2542. An enlarged view 2524A'is shown. Antenna 2524B'can be configured to radiate a signal with a longitudinal electric field directed east or west, as briefly discussed. It will be appreciated that instead of the dipole antenna 2524B'of FIG. 25U, another antenna structure capable of radiating a signal having a longitudinal electric field may be used.

Although two MMICs 2524'are shown within each half of chamber 2525 of the waveguide device 2522, it will be appreciated that more MMICs may be used. For example, FIG. 18W shows a cross section of a cable (transmission medium 2542, etc.) enclosed by a waveguide device with eight MMICs located at locations: north, south, east, west, northeast, northwest, southeast, and southwest. The figure is shown. The two MMIC 2524'shown in FIG. 25U can be viewed as the MMIC 2524' located at the north and south positions shown in FIG. 18W for illustrative purposes. The waveguide device 2522 of FIG. 25U can be further configured with the MMIC 2524'at the west and east positions, as shown in FIG. 18W. In addition, the waveguide device 2522 of FIG. 25U can be further configured with MMICs at northwest, northeast, southwest, and southeast positions, as shown in FIG. 18W. Therefore, the waveguide device 2522 can be configured with more MMICs than the two MMICs shown in FIG. 25U.

With this in mind, here we focus on FIGS. 25V, 25W, 25X, which are non-limiting examples of wave modes and electromagnetic field plots according to the various aspects described herein. Embodiment is shown. FIG. 25V shows an electric field in TM01 wave mode. The electric field is shown in a cross-sectional view (top) and a vertical cross-sectional view (bottom) of a coaxial cable having a central conductor whose outer conductor shield is separated by an insulator. FIG. 25W shows an electric field in TM11 wave mode. The electric field is also shown in a cross-sectional view and a vertical cross-sectional view of a coaxial cable having a central conductor whose outer conductor shield is separated by an insulator. FIG. 25X further shows the electric field in TM21 wave mode. The electric field is shown in a cross-sectional view and a vertical cross-sectional view of a coaxial cable having a central conductor whose outer conductor shield is separated by an insulator.

As shown in the cross section, the TM01 wave mode has a circularly symmetric electric field (ie, an electric field with the same orientation and intensity at different azimuths), while the TM11 and TM21 waves shown in FIGS. 25W and 25X, respectively. The cross section of the mode has a non-circular symmetric electric field (ie, an electric field with different orientations and intensities at different azimuths). The cross-sectional views of the TM11 and TM21 wave modes have a non-circular symmetric electric field, whereas the electric fields in the longitudinal cross-sectional views of the TM01, TM11 and TM21 wave modes are such that the electric field structure of the TM11 wave mode points in the opposite longitudinal direction. It is substantially the same except that the directional electric fields are above and below the conductor, while the longitudinal electric fields above and below the conductor in TM01 and TM21 wave modes point in the same longitudinal direction.

It can be said that the vertical cross-sectional views of the coaxial cables of FIGS. 25V, 25W, and 25X have the same structural arrangement as the vertical cross-sectional view of the waveguide device 2522 in the region 2506'shown in FIG. 25U. In particular, in FIGS. 25V, 25W, and 25X, the coaxial cable has a central conductor and shield separated by an insulator, while region 2506'of the waveguide device 2522 is the central conductor 2543, chamber 2525. It has a dielectric layer 2544 that is covered with a dielectric material 2544'and shielded by a reflective inner surface 2523 of the waveguide device 2522. The coaxial configuration in region 2506 ″ of the waveguide device 2522 follows the tapered region 2506 ″ of the waveguide device 2522. Similarly, the coaxial configuration follows regions 2508 and 2510 of the waveguide device 2522, but no dielectric material 2544'other than the dielectric layer 2544 of the transmission medium 2542 is present in these regions. In the outer region 2512, the transmission medium 2542 is exposed to the environment (eg, air) and therefore the coaxial configuration no longer exists.

As described above, the electric field structure in the TM01 wave mode is circularly symmetric in the cross-sectional view of the coaxial cable shown in FIG. 25V. For illustration purposes, it is assumed that the waveguide device 2522 of FIG. 25U has four MMICs located in the north, south, west, and east positions, as shown in FIG. 18W. In this configuration, with an understanding of the vertical and horizontal electric field structures of the TM01 wave mode shown in FIG. 25V, the four MMIC2524'of the waveguide device 2522 in FIG. 25U sends the TM01 wave mode onto the transmission medium 2542 from the common signal source. Can be configured to: This can be achieved by configuring the MMIC 2524'in the north, south, east, and west to deliver wireless signals with the same phase (polarity). The wireless signals generated by the four MMIC 2524'are coupled through the overlap of each electric field in the dielectric material 2544'and the dielectric layer 2544 of the chamber 2525 (because both dielectric materials have similar permittivity) and these dielectrics. It forms a TM01 electromagnetic wave 2502'with an electric field structure shown in the vertical and horizontal views of FIG. 25V, which is coupled to the material.

Therefore, the electromagnetic wave 2502'having the TM01 wave mode propagates toward the tapered structure 2522B of the waveguide device 2522, thereby becoming the electromagnetic wave 2504'embed in the dielectric layer 2544 of the transmission medium 2542'in the region 2508. .. In the tapered horn section 2522D, the electromagnetic wave 2504'with the TM01 wave mode expands in the region 2510 and finally exits the waveguide device 2522 without changing the TM01 wave mode.

In another embodiment, the waveguide device 2522 can be configured to deliver a TM11 wave mode with vertical polarity in region 2506'. It radiates a first wireless signal from the signal source that has a phase (polarity) opposite to the phase (polarity) of the second wireless signal radiated from the same source by the South MMIC2524'. This can be achieved by constructing the MMIC 2524'in position. These wireless signals are coupled through the overlap of each electric field and are coupled to the dielectric materials 2544'and 2544, TM11 wave mode (vertical) having the electric field structure shown in the vertical and cross-sectional views shown in FIG. 25W. Form an electromagnetic wave with (polarization). Similarly, the waveguide device 2522 can be configured to deliver a TM11 wave mode with horizontal polarity in region 2506'. This constitutes the MMIC 2524'in the eastern position to radiate a first wireless signal having a phase (polarity) opposite to the phase (polarity) of the second wireless signal radiated by the West MMIC 2524'. Can be achieved by.

These wireless signals are coupled through the overlap of each electric field and have the electric field structure shown in the vertical and horizontal cross-sectional views shown in FIG. 25W (but with horizontal polarization), the dielectric materials 2544'and 2544. Form an electromagnetic wave having a TM11 wave mode (horizontally polarized wave) coupled to. Because the TM11 wave modes with horizontal and vertical polarization are orthogonal (ie, the dot product of the corresponding electric field vectors between any pair of these wave modes at each point in space and time produces a sum of zeros). The waveguide device 2522 can be configured to simultaneously deliver these wave modes without interference, thereby allowing wave mode split multiplexing. It should be further noted that the TM01 wave mode is also orthogonal to the TM11 and TM21 wave modes.

The TM11 wave mode remains unchanged while the electromagnetic wave 2502'or 2504' with the TM11 wave mode propagates within the region of the inner surface 2523 of the waveguide device 2522 in the regions 2506', 2506', 2508, and 2510. .. However, when the electromagnetic wave 2504'with the TM11 wave mode exits the region 2512 of the waveguide device 2522, the inner surface 2523 no longer exists and the TM11 wave mode is a hybrid wave mode, especially the EH11 wave mode (vertical polarization, horizontal polarization). , Or both if two electromagnetic waves are transmitted in region 2506').

In yet another embodiment, the waveguide device 2522 can also be configured to deliver the TM21 wave mode in region 2506'. This is the MMIC2524 in the north position so that the first wireless signal having the same phase (polarity) as the second wireless signal generated by the south MMIC2524'is radiated from the same source. It can be achieved by constructing'. At the same time, the MMIC2524'in the west position is configured to radiate a third wireless signal in phase with the fourth wireless signal radiated from the same source by the MMIC2524' located in the east position from the same source. .. However, the north and south MMIC 2524'produces first and second wireless signals with polarities opposite to those of the third and fourth wireless signals produced by the west and east MMIC 2524'. The four alternating polar wireless signals were coupled through the overlap of each electric field and coupled to the dielectric materials 2544'and 2544 having the electric field structure shown in the vertical and cross-sectional views shown in FIG. 25X. , TM21 forms an electromagnetic wave having a wave mode. Upon exiting the waveguide device 2522, the electromagnetic wave 2504'goes into a hybrid wave mode, such as a HE21 wave mode, an EH21 wave mode, or a hybrid wave mode having a different radiation mode (eg, HE2m or EH2m, where m> 1). Can be converted.

25U-25X show some embodiments that utilize the waveguide device 2522 of FIG. 25U to deliver TM01, EH11, and other hybrid wave modes. With an understanding of the electric field structure of other wave modes (eg, TM12, TM22, etc.) propagating on the coaxial cable, the MMIC2524'can cause attenuation of the electric field of electromagnetic waves propagating along the outer surface of the transmission medium 2542. Other wave modes that have a low intensity z-field component and a phi-field component in an electric field structure near the outer surface of the transmission medium 2542 that are useful in reducing propagation loss due to substances such as water, droplets, or other substances. For example, EH12, HE22, etc.) can be further configured to be delivered by other methods.

FIG. 25Y shows a flow chart of a non-limiting embodiment of an example of a method 2560 that transmits and receives electromagnetic waves. The method 2560 transmits or receives a substantially orthogonal wave mode, such as that shown in FIG. 25Z, in order to transmit or receive a wave mode of FIGS. 25A-25D and / or the drawings of the present disclosure (eg, FIGS. 7-14, 25A-25D. It can be applied to other waveguide systems or transmitters described and shown in FIGS. 18N-18W, 22A, 22B, and other drawings). FIG. 25Z shows three cross-sectional views of an insulating conductor in which the TM00 fundamental wave mode, the HE11 wave mode having horizontal polarization, and the HE11 wave mode having vertical polarization propagate. The electric field structure shown in FIG. 25Z can change over time and is therefore an exemplary representation at a particular time point or snapshot. The wave modes shown in FIG. 25Z are orthogonal to each other. That is, the dot product of the corresponding electric field vectors between any pair of wave modes at each point in space and time produces a sum of zeros. Due to this characteristic, the TM00 wave mode, the HE11 wave mode with horizontal polarization, and the HE11 wave mode with vertical polarization can simultaneously propagate along the surface of the same transmission medium in the same frequency band without signal interference. it can.

With this in mind, method 2560 can be initiated in step 2562, where the waveguide system of the present disclosure is a source (eg, a base station, a waveguide system as described herein. The antenna can be configured to receive a communication signal from a wireless signal transmitted by a mobile or stationary device, or from another source. The communication signal is, for example, a communication modulated according to a specific signaling protocol (eg, LTE, 5G, DOCSIS, DSL, etc.) operating in the original frequency band (eg, 900 MHz, 1.9 GHz, 2.4 GHz, 5 GHz, etc.). It can be a signal, a baseband signal, an analog signal, another signal, or any combination thereof. In step 2564, the waveguide system up-converts (or, in some cases, down-converts) such a communication signal to one or more operating frequencies of the plurality of electromagnetic waves, thereby producing the plurality of electromagnetic waves according to the communication signal. It can be configured to be generated or transmitted on a transmission medium. The transmission medium can be an insulating conductor as shown in FIG. 25AA, or a non-insulated conductor that undergoes environmental exposure and oxidizes (or other chemical reaction based on environmental exposure), as shown in FIGS. 25AB and 25AC. Can be. In other embodiments, the transmission medium can be a dielectric material such as the dielectric core shown in FIG. 18A.

To avoid interference, the waveguide system uses TM00 wave mode to generate the first electromagnetic wave and HE11 wave mode with horizontal polarization to generate the second electromagnetic wave and vertically polarized waves in step 2564. It can be configured to simultaneously emit a third electromagnetic wave using the HE11 wave mode it has-see Figure 25Z. Since the first, second, and third electromagnetic waves are orthogonal (ie, do not interfere), they can be transmitted in the same frequency band without interference or with a small amount of acceptable interference. Combining and transmitting three orthogonal electromagnetic wave modes in the same frequency band contributes to some form of wave mode division multiplexing that provides a means of increasing the information bandwidth by a factor of three. By combining the principle of frequency split multiplexing with wave mode split multiplexing, the bandwidth will be TM00 in the second frequency band which does not overlap the first frequency band of the first, second and third orthogonal electromagnetic waves. Wave mode is used to send a fourth electromagnetic wave, HE11 wave mode with horizontal polarization is used to send a fifth electromagnetic wave, and HE11 wave mode with vertical polarization is used to send a sixth electromagnetic wave. It can be further increased by configuring the waveguide system to send out. It will be appreciated that wave mode division multiplexing and other types of multiplexing can be used in combination, in addition to or instead, without departing from the embodiments.

To indicate this point, it is considered that each of the three orthogonal electromagnetic waves in the first frequency band supports a transmission bandwidth of 1 GHz. It is further considered that each of the three orthogonal electromagnetic waves in the second frequency band also supports a transmission bandwidth of 1 GHz. With three wave modes operating in two frequency bands, electromagnetic surface waves utilizing these wave modes allow an information bandwidth of 6 GHz for the transmission of communication signals. If more frequency bands are used, the bandwidth can be further increased.

Here, it is considered that a transmission medium in the form of an insulating conductor (see FIG. 25A) is used for surface wave transmission. It is further considered that the transmission medium has a dielectric layer having a thickness proportional to the radius of the conductor (for example, a conductor having a radius of 4 mm and an insulating layer having a thickness of 4 mm). With this type of transmission medium, the waveguide system can be configured to choose from several options for transmitting electromagnetic waves. For example, in step 2564, the waveguide system uses wave mode split multiplexing in the first frequency band (eg, 1 GHz) to transmit the first to third electromagnetic waves and the second frequency band (eg, 1 GHz). 2.1 GHz) using wave mode split multiplexing to transmit the third and fourth electromagnetic waves, and using wave mode split multiplexing in the third frequency band (eg 3.2 GHz) from seventh to seventh. A ninth electromagnetic wave can be transmitted and configured to be similar below. Assuming that each electromagnetic wave supports a bandwidth of 1 GHz, the first to ninth electromagnetic waves can collectively support a bandwidth of 9 GHz.

Instead of or at the same time transmitting an electromagnetic wave having an orthogonal wave mode in step 2564, the waveguide system is configured to transmit one or more high frequency electromagnetic waves (eg, millimeter waves) on an insulating conductor in step 2564. can do. In one embodiment, the one or more high frequency electromagnetic waves are, as described above, such as TM0m wave mode and EH1m wave mode (here m> 0) or HE2m wave mode (here m> 1). It can be configured in non-overlapping frequency bands according to one or more corresponding wave modes that are less susceptible to the water film. In other embodiments, the waveguide system may instead be susceptible to water, but nevertheless longitudinal and / or azimuth exhibiting low propagation loss when the transmission medium is dry. It can be configured to transmit one or more high frequency electromagnetic waves in non-overlapping frequency bands according to one or more corresponding wave modes having an angular field near the surface of the transmission medium. Thus, the waveguide system can be configured to transmit several combinations of wave modes on the insulating conductor (and a dielectric-only transmission medium such as a dielectric core) when the insulating conductor is dry. ..

Here, it is considered that a transmission medium in the form of a non-insulated conductor (see FIGS. 25AB and 25AC) is used for surface wave transmission. It is further believed that non-insulated or bare conductors are exposed to environments subject to varying levels of humidity and / or rain (and atmospheric gases such as air and oxygen). Non-insulated conductors, such as overhead power lines and other non-insulated wires, are often made of aluminum, sometimes reinforced with steel. Aluminum can react naturally with water and / or air to form aluminum oxide. The aluminum oxide layer can be a thin layer (eg, nano-micrometer thick). The aluminum oxide layer has dielectric properties and can therefore function as a dielectric layer. Therefore, the non-insulated conductor can be used not only in TM00 wave mode, but also in HE11 wave mode having horizontally polarized waves and HE11 wave mode having vertically polarized waves at high frequencies, at least partially based on the thickness of the oxide layer. Other wave modes can also propagate. Therefore, a non-insulating conductor having a dielectric layer formed in an environment such as an oxide layer can be used for transmission of electromagnetic waves using wave mode division multiplexing and frequency division multiplexing. Other electromagnetic waves having a wave mode (with or without cutoff frequency) capable of propagating over the oxide layer are also intended by the present disclosure and can be applied to the embodiments described herein.

In one embodiment, the term "environmentally formed dielectric layer" refers to non-insulated conductors exposed to the environment that are not artificially created in the laboratory or other controlled settings (eg, on electrical columns or other). It can represent a bare conductor exposed to air, moisture, rain, etc. in an exposed environment). In other embodiments, the dielectric layer formed in the environment provides a non-insulating conductor in a controlled environment (eg, controlled humidity or other gaseous material) that forms a dielectric layer on the outer surface of the non-insulating conductor. It can be formed in a controlled setting such as a manufacturing facility to be exposed. In yet another alternative embodiment, the non-insulated conductor facilitates a chemical reaction with other substances / compounds available in the natural environment or in an artificially created laboratory or controlled setting, thereby facilitating a chemical reaction. It is also possible to "dope" certain substances / compounds (eg, reactants) that form a dielectric layer formed in the environment.

Wave mode division multiplexing and frequency division multiplexing can prove to be useful in reducing obstacles such as water accumulation on the outer surface of a transmission medium. To determine if obstacle mitigation is needed, the waveguide system can be configured in step 2566 to determine if an obstacle is present on the transmission medium. A film of water (or water droplets) that collects on the outer surface of a transmission medium due to rainfall, condensation, and / or excessive moisture can be a form of obstacle that, if not mitigated, can cause transmission loss of electromagnetic waves. .. Other objects coupled to the junction of the transmission medium or the outer surface of the transmission medium can also function as obstacles.

Obstacles can be detected by a source waveguide system that transmits electromagnetic waves over a transmission medium and measures reflected electromagnetic waves based on these transmissions. Alternatively or in combination thereof, the source waveguide system receives the electromagnetic waves transmitted by the source waveguide system and receives a communication signal (wireless or electromagnetic waves) from the received waveguide system that performs quality measurements on the electromagnetic waves. By receiving, obstacles can be detected. In step 2566, if an obstacle is detected, the waveguide system can be configured to identify options for updating, modifying, or otherwise modifying the electromagnetic wave being transmitted.

For example, in the case of an insulated conductor, the waveguide system has a frequency band starting at 30 GHz with a large bandwidth (eg, 10 GHz) when the insulated conductor, such as shown in FIG. 25N, is dry in step 2564. It is considered that a higher-order wave mode such as TM01 wave mode is transmitted. The figure in FIG. 25N is based on a simulation that does not take into account all possible environmental conditions or properties of a particular insulating conductor. Therefore, the TM01 wave mode may have a lower bandwidth than shown. However, for illustration purposes, a 10 GHz bandwidth is assumed for electromagnetic waves with TM01 wave mode.

In the present disclosure, it has been mentioned above that the TM01 wave mode has a desirable electric field alignment that is not close to the outer surface in the longitudinal direction and the azimuth, but nevertheless, when a water film (or water droplet) accumulates on the insulating conductor. , Can undergo some signal attenuation, thereby reducing the operating bandwidth. This attenuation is shown in FIG. 25N, where an electromagnetic wave with a TM01 wave mode having a bandwidth of about 10 GHz (30 GHz to 40 GHz) on a dry insulating conductor is about 1 GHz (when the insulating conductor is moist). It is shown that the bandwidth is reduced to 30 GHz to 31 GHz). To reduce bandwidth loss, waveguide systems can be configured to emit electromagnetic waves at much lower frequencies (eg, less than 6 GHz) using wave mode division multiplexing and frequency division multiplexing. it can.

For example, a waveguide system includes a first set of electromagnetic waves, particularly a first electromagnetic wave having a TM00 wave mode in which each electromagnetic wave has a central frequency of 1 GHz, and a second electromagnetic wave having a HE11 wave mode having horizontal polarization. And can be configured to transmit a third electromagnetic wave having a HE11 wave mode with vertical polarization. Assuming that a frequency band of 500 MHz to 1.5 GHz can be used for the transmission of communication signals, each electromagnetic wave can provide a bandwidth of 1 GHz, and can collectively provide a system bandwidth of 3 GHz.

The waveguide system includes a second set of electromagnetic waves, in particular a fourth electromagnetic wave having a TM00 wave mode, each electromagnetic wave having a central frequency of 2.1 GHz, a fifth electromagnetic wave having a HE11 wave mode having horizontal polarization, And it is also considered to be configured to transmit a sixth electromagnetic wave having a HE11 wave mode with vertical polarization. Assuming a frequency band of 1.6 GHz to 2.6 GHz, a protected band of 100 MHz between the first set of electromagnetic waves and the second set of electromagnetic waves, each electromagnetic wave can provide a bandwidth of 1 GHz. Together, an additional bandwidth of 3 GHz can be provided, thereby providing a system bandwidth of up to 6 GHz.

The waveguide system includes a third set of electromagnetic waves, particularly a seventh electromagnetic wave having a TM00 wave mode, each electromagnetic wave having a central frequency of 3.2 GHz, and an eighth electromagnetic wave having a HE11 wave mode having horizontal polarization. And it is further considered to be configured to transmit a ninth electromagnetic wave having a HE11 wave mode with vertical polarization. Assuming a frequency band of 2.7 GHz to 3.7 GHz, a protected band of 100 MHz between the second set of electromagnetic waves and the third set of electromagnetic waves, each electromagnetic wave can provide a bandwidth of 1 GHz. Together, an additional bandwidth of 3 GHz can be provided, thereby providing a system bandwidth of up to 9 GHz.

The combination of the TM01 wave mode and the three sets of electromagnetic waves configured for wave mode split multiplexing and frequency division multiplexing provides a total system bandwidth of 10 GHz, which allows the high frequency electromagnetic waves having the TM01 wave mode. Restores the previously available 10 GHz bandwidth when propagating over dry insulating conductors. FIG. 25AD shows the process of performing the mitigation of TM01 wave mode receiving obstacles such as water film detected in step 2566. FIG. 25AD is combined with low frequency TM00 and HE11 wave modes configured according to Wave Mode Division Multiplexing (WMDM) and Frequency Division Multiplexing (FDM) schemes from dry insulated conductors supporting high bandwidth TM01 wave mode. The transition to a damp insulating conductor that supports the low bandwidth TM01 wave mode to recover the system bandwidth loss is shown.

Now consider a non-insulated conductor in which the waveguide system has delivered a TM00 wave mode with a frequency band starting at 10 GHz with a large bandwidth (eg, 10 GHz) in step 2564. Here, it is considered that the transmission medium propagating in the 10 GHz TM00 wave mode is exposed to obstacles such as water. As mentioned above, the high frequency TM00 wave mode on the insulating conductor undergoes a considerable amount of signal attenuation when a water film (or water droplet) accumulates on the outer surface of the insulating conductor (eg, 45 dB / M at 10 GHz-Figure. See 25J). Similar attenuation exists in the 10 GHz (or higher) TM00 wave mode propagating over "non-insulated" conductors. However, a non-insulated conductor (eg, aluminum) exposed to the environment can have an oxide layer formed on the outer surface, and the oxide layer is in a wave mode other than TM00 (eg, HE11 wave mode). It can function as a supporting dielectric layer. It should be further noted that at low frequencies, the TM00 wave mode propagating on the insulating conductor exhibits much lower attenuation (eg, 0.62 dB / M at 4 GHz-see Figure 25J). TM00 wave mode operating below 6 GHz also also exhibits low propagation loss on non-insulated conductors. Therefore, in order to reduce bandwidth loss, the waveguide system is an electromagnetic wave having a TM00 wave mode at low frequencies (eg, 6 GHz or less) and an electromagnetic wave having a HE11 wave mode configured for WMDM and FDM at high frequencies. Can be configured to send.

With reference to FIG. 25Y again, it is considered that the waveguide system detects obstacles such as water on the non-insulated state exposed in the environment in step 2566. The waveguide system can be configured to reduce interference by transmitting a first electromagnetic wave configured using the TM00 wave mode with a center frequency of 2.75 GHz. Assuming that a frequency band of 500 MHz to 5.5 GHz is available for the transmission of communication signals, electromagnetic waves can provide a system bandwidth of 5 GHz.

FIG. 25AF provides a diagram of an electric field plot of HE11 wave mode at 200 GHz on a bare conductor with a thin aluminum oxide layer (4 μm). The plot shows the magnitude of the field intensities of the low, phi, and z field components at the peak, as a function of the radial distance away from the center of the bare conductor. The field intensities were calculated based on the absence of water, but the z-field and phi-field components of the electric field start from the outer surface of the oxide layer and are occupied by the water film, as shown in FIG. 25AF. Through the possible positions, it can have a very small field strength relative to the size of the radial row field.

Assuming an oxide layer or other dielectric layer comparable in size in the plot of FIG. 25AF, the waveguide system has each electromagnetic wave with a center frequency of 200 GHz (other lower or higher center frequencies can also be used). It can be configured to transmit a second electromagnetic wave having a horizontally polarized HE11 wave mode and a third electromagnetic wave having a vertically polarized HE11 wave mode. Assuming that each electromagnetic wave is configured according to the HE vertically polarized wave mode and the HE horizontally polarized wave mode having a 2.5 GHz bandwidth, these waves together provide an additional bandwidth of 5 GHz. By combining the low frequency TM00 wave mode with the high frequency HE wave mode, the system bandwidth can be restored to 10 GHz. It will be appreciated that depending on the thickness of the oxide layer, the properties of the non-insulated conductor, and / or other environmental factors, HE wave modes at other center frequencies and bandwidths may also be possible.

FIG. 25AE shows the process of performing mitigation of the high frequency TM00 wave mode subject to obstacles such as water film detected in step 2566. FIG. 25AD shows a system bandwidth loss by combining a low frequency TM00 wave mode with a high frequency HE11 wave mode configured according to the WMDM and FDM schemes from a dry non-insulated conductor supporting the high bandwidth TM00 wave mode. Shows a transition to a damp, non-insulated conductor that recovers.

It will be understood that the above mitigation techniques are non-limiting. For example, the center frequencies mentioned above can vary from system to system. Moreover, the original wave mode used before the obstacle was detected can be different from the above illustration. For example, in the case of an insulated conductor, the EH11 wave mode can be used alone or in combination with the TM01 wave mode. It is also understood that electromagnetic waves can be transmitted using WMDM and FDM techniques at any time, not just when obstacles are detected in step 2566. It is further understood that other wave modes capable of supporting WMDM and / or FDM techniques can be applied and / or combined with the embodiments described in this disclosure and are therefore intended by this disclosure. To.

With reference to FIG. 25Y again, if the mitigation scheme using WMDM and / or FDM is determined according to the above example, the waveguide system is one or more in step 2568 before the update is performed in step 2570. It can be configured to notify one or more other waveguide systems of mitigation schemes intended to be used to update multiple electromagnetic waves. Notifications can be transmitted wirelessly to one or more other waveguide systems using an antenna if the signal degradation in the electromagnetic waves is too severe. If signal attenuation is acceptable, the notification can be transmitted via the affected electromagnetic wave. In another embodiment, the waveguide system can be configured to skip step 2568 and in step 2570 perform mitigation schemes using WMDM and / or FDM without notice. This embodiment can be applied, for example, if other receiving waveguide systems know in advance which type of mitigation scheme will be used, or the receiving waveguide system is a signal detection technique. Is configured to use to discover mitigation schemes. When the mitigation scheme using WMDM and / or FDM is initiated in step 2570, the waveguide system continues to deliver the received communication signal in steps 2562 and 2564 as described above using the electromagnetic waves of the updated configuration. Can be processed.

At step 2566, the waveguide system can monitor whether obstacles are still present. This determination is made by transmitting a test signal (eg, an electromagnetic surface wave in the original wave mode) to another waveguide system and, if the situation improves, waiting for the test result from the waveguide system and / or transmitting. It can be performed by using other obstacle detection techniques such as a signal reflection test based on the tested signal. If it is determined that the obstacle has been removed (eg, the transmission medium has dried), the waveguide system proceeds to step 2572, where WMDM and / or FDM is used as a mitigation technique to perform signal updates at step 2568. It can be judged that it was done. The waveguide system is then configured in step 2568 to notify the receiving waveguide system of its intention to restore transmission to the original wave mode, or to bypass this step and proceed to step 2570. And in step 2570, recover transmission to the original wave mode and assume that the receiving waveguide system knows the original wave mode and the corresponding transmission parameters, or otherwise detect this change. can do.

The waveguide system can also be configured to receive electromagnetic waves configured for WMDM and / or FDM. For example, it is considered that an electromagnetic wave having a high bandwidth (for example, 10 GHz) TM01 wave mode is propagating on an insulating conductor as shown in FIG. 25AD, and the electromagnetic wave is generated by the source waveguide system. In step 2582, the receiving waveguide system can be configured to process a single electromagnetic wave with TM01 wave mode under normal circumstances. However, it is believed that the source waveguide system transitions to transmitting electromagnetic waves using WMDM and FDM with a TM01 wave mode that uses a low bandwidth on the insulating conductor, as described above in FIG. 25AD. In this case, the receiving waveguide system needs to process multiple electromagnetic waves in different wave modes. In particular, the receiving waveguide system uses WMDM and FDM to process each of the 1st to 9th electromagnetic waves in step 2582 and selectively selects the electromagnetic waves using TM01 wave mode, as shown in FIG. 25AD. It is configured to process.

When one or more electromagnetic waves are received in step 2582, the received waveguide is used by the source waveguide system in step 2564 (and / or, if updated, step 2570) using signal processing techniques. It can be configured to acquire the communication signal transmitted by the generated electromagnetic wave. At step 2586, the receiving waveguide system can also determine if the source waveguide system has updated the transmission scheme. Updates can be detected from the data provided in the electromagnetic waves transmitted by the source waveguide system or from the wireless signals transmitted by the source waveguide system. In the absence of updates, the receiving waveguide system can continue to receive and process electromagnetic waves in steps 2582 and 2584, as described above. However, if an update is detected in step 2586, the receiving waveguide system proceeds to step 2588 to coordinate the update with the source waveguide system and then, as described above, in steps 2582 and 2584, the updated electromagnetic wave. Can be received and processed.

It will be appreciated that Method 2560 can be used in any communication scheme, including simple and dual communication between waveguide systems. Therefore, a source waveguide system that performs an update to transmit an electromagnetic wave according to another wave mode then causes the receiving waveguide system to perform a similar step of returning the electromagnetic wave transmission. The above embodiment related to the method 2560 of FIG. 25Y and the embodiment shown in FIGS. 25Z to 25AE are on the outer surface of a transmission medium (for example, an insulated conductor, a non-insulated conductor, or any transmission medium having a dielectric outer layer). It will also be appreciated that it may be combined in whole or in part with other embodiments of the present disclosure to reduce the propagation loss caused by obstacles in or near it. Obstacles are placed on or near liquids (eg, water), solid objects placed on the outer surface of the transmission medium (eg, ice, snow, joints, tree branches, etc.), or on the outer surface of the transmission medium. Can be any other object.

For brevity, each process is shown and described as a series of blocks in FIG. 25Y, but the claims are not limited by the order of the blocks and some blocks are described herein. It should be understood and recognized that it can be performed in a different order than shown and described in and / or at the same time as other blocks. Moreover, not all of the blocks shown are required to carry out the methods described herein.

Here, with reference to FIGS. 25AG and 25AH, a block diagram showing a non-limiting embodiment of an example of transmitting an orthogonal wave mode by the method 2560 of FIG. 25Y is shown. FIG. 25AG shows an embodiment of simultaneously transmitting a TM00 wave mode, a HE11 wave mode having vertical polarization, and a HE11 wave mode having horizontal polarization, as shown at some point in FIG. 25Z. In one embodiment, these orthogonal wave modes have eight MMICs shown in FIG. 18 arranged in symmetrical positions (eg, north, northeast, east, southeast, south, southwest, west, and northwest). It can be transmitted using a waveguide transmitter. These eight MMICs can be configured in the waveguide transmitter of FIG. 18R (or FIG. 18T). Further, the waveguide transmitter comprises a cylindrical sleeve 2523A and a tapered dielectric wound around a transmission medium (eg, an insulated conductor, a non-insulated conductor, or another cable having a dielectric layer such as a dielectric core). be able to. The housing assembly of the waveguide transmitter (not shown) is configured to include a mechanism (eg, a hinge) that allows the longitudinal opening of the waveguide transmitter to be placed around the transmission medium and latched. be able to.

With these configurations in mind, the waveguide transmitter can include three transmitters (TX1, TX2, and TX3) coupled to MMICs with different coordinate positions (see FIGS. 25AG and 18W). ). Interconnects between transmitters (TX1, TX2, and TX3) and MMICs can be performed using common printed circuit boards or other suitable interconnect techniques. The first transmitter (TX1) can be configured to transmit the TM00 wave mode and the second transmitter (TX2) can be configured to transmit the HE11 vertically polarized wave mode. , The third transmitter (TX3) can be configured to transmit the HE11 horizontally polarized wave mode.

The first signal port (denoted as "SP1") of the first transmitter (TX1) can be coupled parallel to each of the eight MMICs. The second signal port (denoted as "SP2") of the first transmitter (TX1) can be coupled to the conductive sleeve 2523A disposed on the transmission medium by the waveguide transmitter as described above. The first transmitter (TX1) can be configured to receive the first group of communication signals described in step 2562 of FIG. 25Y. The first group of communication signals is frequency-shifted from the original frequency by the first transmitter (TX1) in order to place the communication signals in order on the first electromagnetic channel configured according to the TM00 wave mode. Can (if needed). Eight MMICs coupled to a first transmitter (TX1) group a first group of communication signals at the same center frequency (eg, 1 GHz for a first electromagnetic wave, as described in connection with FIG. 25AD). ) Can be configured to be up-converted (or down-converted). All eight MMICs have a synchronous reference oscillator that can be phase-locked using various synchronization techniques.

Since the eight MMICs receive signals from the first signal port of the first transmitter (TX1) based on the criteria provided by the second signal port, the eight MMICs are thereby of the same polarity. Receive a signal. Thus, when these signals are up-converted (or down-converted) and processed for transmission by the eight MMICs, each one or more antennas of the eight MMICs simultaneously emit signals with the same polarity of electric field. Radiate. Collectively, MMICs that are in opposite positions (eg, north MMICs and south MMICs) will have an electric field structure that is aligned towards or away from the transmission medium, thereby at a particular point in time. , Generates an outward field structure such as the TM00 wave mode shown in FIG. 25Z. It will be appreciated that at other times, the field structure shown in FIG. 25Z radiates inward due to the constant vibration of the signals emitted by the eight MMICs. By radiating electric fields of the same polarity symmetrically, a collection of opposing MMICs can propagate over a transmission medium with a dielectric layer and transmit a first group of communication signals to a receiving waveguide system. It contributes to the induction of the first electromagnetic wave having a wave mode.

Here, referring to the second transmitter (TX2) in FIG. 25AG, this transmitter has a first signal port (SP1) coupled to MMICs located at north, northeast, and northwest positions. On the other hand, the second signal port (SP2) of the second transmitter (TX2) is coupled to MMICs located in the south, southeast, and southwest positions (see FIG. 18W). The second transmitter (TX2) receives a second group of communication signals described in step 2562 of FIG. 25Y, which is different from the first group of communication signals received by the first transmitter (TX1). Can be configured to: A second group of communication signals is originally by a second transmitter (TX2) to place the communication signals in order on a second electromagnetic channel configured according to the HE11 wave mode with vertically polarized waves. Frequency can be shifted from frequency (if required). The six MMICs coupled to the second transmitter (TX2) have a second communication signal at the same center frequency as that used for the TM00 wave mode (ie, 1 GHz as described in connection with FIG. 25AD). Groups can be configured to be up-converted (or down-converted). Since the TM00 wave mode is orthogonal to the HE11 wave mode having vertically polarized waves, it is possible to share the same center frequency within the overlapping frequency bands without interference.

With reference to FIG. 25AG again, the first signal port (SP1) of the second transmitter (TX2) produces a signal having the opposite polarity to the signal of the second signal port (SP2). As a result, the electric field alignment of the signal generated by one or more antennas of the north MMIC has the opposite polarity to the electric field alignment of the signal generated by one or more antennas of the south MMIC. become. Thus, the north and south MMIC electric fields have a vertically aligned electric field structure in the same direction, thereby north, such as the HE11 wave mode with vertical polarity shown in FIG. 25Z, at a particular time point. Generate a field structure. It will be appreciated that HE11 wave modes have a south field structure at other times due to the constant oscillatory nature of the signals emitted by the north and south MMICs. Similarly, based on the opposite polarities of the signals supplied by the first and second signal ports to the northeast and southeast MMICs, respectively, these MMICs have the vertical polarity shown in FIG. 25Z at a particular time point. Generates a curved electric field structure shown on the east side of the HE11 wave mode. Also, based on the opposite polarities of the signals supplied to the northwest MMIC and the southwest MMIC, these MMICs have a curved field structure shown to the west of the HE11 wave mode with the vertical polarity shown in FIG. 25Z at a particular time point. To generate.

A collection of signals with a directionally aligned field structure by radiating electric fields of opposite polarity with opposite MMICs (north, northeast, and northwest and south, southeast, and southwest) is shown in FIG. 25Z. Contributes to the induction of a second electromagnetic wave having a HE11 wave mode with vertically polarized waves. The second electromagnetic wave propagates along the "same" transmission medium as described above for the first transmitter (TX1). Given the orthogonality of the TM00 wave mode and the HE11 wave mode with vertical polarity, ideally there is no interference between the first and second electromagnetic waves. Therefore, the first and second electromagnetic waves with overlapping frequency bands propagating along the same transmission medium can bring the first and second groups of communication signals to the same (or other) receive waveguide system without problems. Can be communicated.

Here, referring to the third transmitter (TX3) in FIG. 25AG, this transmitter has a first signal port (SP1) coupled to MMICs located at east, northeast, and southeast positions. On the other hand, the second signal port (SP2) of the third transmitter (TX3) is coupled to MMICs located in the west, northwest, and southwest positions (see FIG. 18W). The third transmitter (TX3) is different from the first and second groups of communication signals received by the first transmitter (TX1) and the second transmitter (TX2), respectively, in step 2562 of FIG. 25Y. It can be configured to receive a third group of communication signals as described in. A third group of communication signals is originally by a third transmitter (TX3) to place the communication signals in order on a second electromagnetic channel configured according to the horizontally polarized HE11 wave mode. Frequency can be shifted from frequency (if needed). The six MMICs coupled to the third transmitter (TX3) have the same center frequencies as those used in TM00 wave mode and HE11 wave mode with vertically polarized waves (ie, as described in connection with FIG. 25AD). A third group of communication signals can be configured to be up-converted (or down-converted) to 1 GHz). Since the TM00 wave mode, the HE11 wave mode with vertically polarized waves, and the HE11 wave mode with horizontally polarized waves are orthogonal, they can share the same center frequency within the overlapping frequency bands without interference.

With reference to FIG. 25AG again, the first signal port (SP1) of the third transmitter (TX3) produces a signal having the opposite polarity to the signal of the second signal port (SP2). As a result, the electric field alignment of the signal generated by one or more antennas of the east MMIC has the opposite polarity to the electric field alignment of the signal generated by the one or more antennas of the west MMIC. Therefore, the electric fields of the East MMIC and the West MMIC will have an electric field structure that is horizontally aligned in the same direction, thereby in the HE11 wave mode with horizontal polarization shown in FIG. 25Z at a particular time point. To generate a western structure like this. It will be appreciated that HE11 wave modes have an eastern field structure at other times due to the constant oscillations of the signals emitted by the east and west MMICs. Similarly, based on the opposite polarities of the signals supplied by the first and second signal ports to the northeast MMIC and northwest MMIC, respectively, these MMICs at a particular point in time have the horizontally polarized waves shown in FIG. 25Z. Generates a curved electric field structure shown on the north side of the HE11 wave mode having. Also, based on the opposite polarities of the signals supplied to the southeast and southwest MMICs, these MMICs at a particular time point have a curved electric field shown on the south side of the HE11 wave mode with horizontal polarization shown in FIG. 25Z. Generate a structure.

A collection of signals with a directionally aligned field structure by radiating electric fields of opposite polarities from opposing MMICs (east, northeast, and southeast and west, northwest, and southwest) is shown in FIG. 25Z. It contributes to the induction of a third electromagnetic wave having a HE11 wave mode having horizontally polarized waves. The third electromagnetic wave propagates along the "same" transmission medium as described above for the first transmitter (TX1) and the second transmitter (TX2). Ideally, given the orthogonality of TM00 wave mode, HE11 wave mode with vertically polarized waves, and HE11 wave mode with horizontally polarized waves, a first electromagnetic wave, a second electromagnetic wave, and a third electromagnetic wave. There is no interference in between. Thus, the first, second, and third electromagnetic waves with overlapping frequency bands propagating along the same transmission medium share the same (or other) first, second, and third groups of communication signals. It can be transmitted to the receiving waveguide system without any problem.

Due to the orthogonality of the electromagnetic waves described above, the receiving waveguide system has a first electromagnetic wave having a TM00 wave mode, a second electromagnetic wave having a HE11 wave mode having vertically polarized waves, and a HE11 wave mode having horizontally polarized waves. It can be configured to selectively extract a third electromagnetic wave. After processing each of these electromagnetic waves, the receiving waveguide system can be further configured to acquire first, second, and third groups of communication signals transmitted by these waves. FIG. 25AH shows a block diagram that selectively receives each of the first, second, and third electromagnetic waves.

In particular, the first electromagnetic wave having the TM00 wave mode takes the difference between the signal received by all eight MMICs and the signal reference provided by the metal sleeve 2523A, as shown in the block diagram in FIG. 25AI. As a result, it can be selectively received by the first receiver (RX1) shown in FIG. 25AH. The second electromagnetic wave having the HE11 wave mode with vertically polarized waves is the signal received by the MMICs located at the north, northeast, and northwest positions, and the south, southeast, as shown in the block diagram in FIG. 25AJ. , And by taking the difference from the signal received by the MMIC located at the southwest position, it can be selectively received by the second receiver (RX2) shown in FIG. 25AH. The third electromagnetic wave with the HE11 wave mode with horizontal polarization is the signal received by the MMICs located in the east, northeast, and southeast positions, and the west, northwest, as shown in the block diagram in FIG. 25AK. , And by taking the difference from the signal received by the MMIC located at the southwest position, it can be selectively received by the third receiver (RX3) shown in FIG. 25AH.

FIG. 25AL shows a simplified function block diagram of a MMIC. The MMIC may, for example, set one of the communication signals supplied by one of the signal ports (SP1 or SP2) of the transmitter (TX1, TX2, or TX3) to the desired center frequency according to the configuration shown in FIG. 25AG. A mixer coupled to a reference (TX) oscillator that shifts to is available. For example, in the case of TX1, the communication signal from SP1 is supplied to each transmission path of the MMIC (that is, NE, NW, SE, SW, N, S, E, and W). In the case of TX2, the communication signal from SP1 is supplied to another transmission path of three MMICs (that is, N, E, and NW). The transmission path used by MMICs N, E, and W for the communication signal supplied by SP1 of TX2 is different from the transmission path used by MMIC for the communication signal supplied by SP1 of TX1. .. Similarly, the communication signal from SP2 of TX2 is supplied to another transmission path of the other three MMICs (that is, S, SE, and SW). Again, the transmission path used by the MMIC S, SE, and SW for the communication signal supplied by the SP2 of the TX2 is the transmission used by the MMIC for the communication signal from the SP1 of the TX1 and the SP1 of the TX2. Different from the route. Finally, in the case of TX3, the communication signal from SP1 is supplied to yet another transmission path of the three MMICs (ie, E, NE, and SE). The transmission path used for MMIC E, NE, and SE for the communication signal from SP1 of TX3 is by MMIC for the communication signal supplied by SP1 of TX1, SP1 of TX2, and SP2 of TX2. Different from the transmission route used. Similarly, the communication signal from SP2 of TX3 is supplied to another transmission path of the other three MMICs (that is, W, NW, and SW). Again, the transmission paths used by the MMICs W, NW, and SW for the communication signals supplied by the TX3 SP2 are the communication signals from the TX1 SP1, TX2 SP1, TX2 SP2, and TX3 SP1. Different from the transmission path used by MMICs for.

When the communication signal is frequency-shifted by the mixer shown in the transmission path, the frequency-shifted signal generated by the mixer can be filtered by a band path filter that removes the spurious signal. Therefore, the output of the band path filter can be provided to the power amplifier coupled to the antenna by a duplexer that radiates the signal as described above. A duplexer can be used to separate the transmit path from the receive path. The figure in FIG. 25AL is deliberately oversimplified to facilitate illustration.

It is understood by the present disclosure that other components (not shown) such as impedance matching circuits, phase-locked loops, or other suitable components that improve the accuracy and efficiency of transmit (and receive) paths are intended. Yeah. Further, while each MMIC can implement a single antenna, other designs with multiple antennas can be utilized as well. In order to achieve two or more orthogonal wave modes with overlapping frequency bands (eg, TM00 wave mode, HE11 vertical wave mode, and HE11 horizontal wave mode described above), the same reference oscillator is used to N the transmission path. It will be further understood that it can be repeated times. N may represent an integer associated with the number of MMICs used to generate each wave mode. For example, in FIG. 25AG, the MMIC NE is used 3 times, thus the MMIC NE has 3 transmission paths (N = 3), the MMIC NW is used 3 times, and therefore the MMIC NW has 3 transmission paths. (N = 3), the MMIC N is used twice, so the MMIC N has two transmission paths (N = 2) and so on. When frequency division multiplexing is used to generate the same wave mode in other frequency bands (see FIGS. 25AD and 25AE), the transmission path uses different reference oscillators centered around the other frequency bands. It can be repeated further.

In the reception path shown in FIG. 25AL, the N signals supplied by the N antennas via the duplexer of each transmission path in the MMIC can be filtered by the corresponding N band path filters, and the band path can be filtered. The filter supplies the output to N low noise amplifiers. Therefore, the N low noise amplifiers supply the signals to the N mixers to generate N intermediate frequency received signals. As before, N represents the number of times an MMIC is used to receive a wireless signal in different wave modes. For example, in FIG. 25AH, the MMIC NE is used 3 times, thus the MMIC NE has 3 receive paths (N = 3), the MMIC N is used twice, and therefore the MMIC N has 2 receive paths. (N = 2), and so on.

Referring again to FIG. 25AL, the Y receive signals (or reference from the metal sleeve 2523A of FIG. 25D) supplied by the receive path of a particular MMIC to reconstruct the wave mode signal are from FIGS. 25AI to FIG. It is subtracted from the X received signals supplied by the other MMICs based on the configuration shown in 25AK. For example, the TM00 signal is reconstructed by supplying the received signals of all MMICs (NE, NW, SE, SW, N, S, E, W) to the plus port of the summarizer (ie, the X signal). On the other hand, the reference signal from the metal sleeve 2523A of FIG. 25D is supplied to the minus port of the summer (ie, Y signal) -see FIG. 25AI. The difference between the X signal and the Y signal becomes the TM00 signal. To reconstruct the HE11 vertical signal, the received signals of MMIC N, NE, and NW are fed to the plus port of the summer (ie, the X signal), while the received signals of MMIC S, SE, and SW are , Supplied to the minus port of the summer (ie, Y signal) -see Figure 25AJ. The difference between the X signal and the Y signal becomes the HE11 vertical signal. Finally, in order to reconstruct the HE11 horizontal signal, the received signals of MMIC E, NE, and SE are supplied to the plus port of the summer (ie, the X signal), while the MMIC W, NW, and SW The received signal is supplied to the minus port of the summer (ie, the Y signal) -see Figure 25AK. The difference between the X signal and the Y signal becomes the HE11 horizontal signal. Since there are three wave mode signals to be reconstructed, the block diagram of the summarizer with the X and Y signals is repeated three times.

Each of these reconstructed signals is at an intermediate frequency. These intermediate frequency signals are provided to receivers (RX1, RX2, and RX3) that include circuits (eg, DSPs, A / D converters, etc.) that process and selectively acquire communication signals from them. Similar to the transmit path, the reference oscillators of the three receive paths can be configured to be synchronized using a phase-locked loop technique or other suitable synchronization technique. If frequency division multiplexing is used for the same wave mode in other frequency bands (see FIGS. 25AD and 25AE), the receive path may be repeated using different reference oscillators centered on the other frequency bands. it can.

It will be appreciated that other suitable designs that can serve as alternative embodiments to the embodiments shown in FIGS. 25AG-25AL can be used for transmission and reception of orthogonal wave modes. For example, there may be fewer or more MMICs than described above. Slotted transmitters as shown in FIGS. 18N-18O, 18Q, 18S, 18U, and 18V can be used in place of or in combination with MMICs. It is further understood that more or fewer sophisticated components can be used by transmitting or receiving in orthogonal wave mode. Therefore, other suitable design and / or functional components for transmission and reception of orthogonal wave modes are contemplated by the present disclosure.

Here, with reference to FIG. 26, a block diagram of a computing environment according to various aspects described herein is shown. To provide further context with respect to the various embodiments described herein, FIG. 26 and the following studies are suitable computing environments 2600 capable of implementing the various embodiments of the embodiments of the present disclosure. It is intended to provide a concise and general description of. Although embodiments have been described in the general context of computer executable instructions that can be executed on one or more computers, those embodiments can be combined with other program modules and / or hardware. Those skilled in the art will recognize that it can be implemented as a combination of hardware and software.

In general, a program module includes routines, programs, components, data structures, etc. that perform a particular task or perform a particular abstract data type. In addition, single-processor or multiprocessor computer systems, mini-computers, mainframe computers and personal computers, handheld computing devices, micros, which can operably combine the methods of the invention into one or more related devices, respectively. It will be appreciated by those skilled in the art that it can be implemented with other computer system configurations, including processor-based or programmable household appliances.

As used herein, a processing circuit processes and responds to processors and other application-specific circuits such as application-specific integrated circuits, digital logic circuits, state machines, programmable gate arrays, or input signals or data. Includes other circuits that generate output signals or data. It should be noted that any function and feature described herein in relation to the operation of the processor can also be performed by the processing circuit.

Terms such as "first", "second", "third", etc., when used in the claims, are for the purpose of clarification only, unless otherwise specified by the context. In other respects, it does not indicate or imply any order in terms of time. For example, the "first judgment", "second judgment" and "third judgment" neither indicate nor imply that the first judgment is made before the second judgment. The reverse is also true.

Illustrative embodiments of embodiments herein can also be performed in a distributed computing environment in which specific tasks are performed by remote processing devices linked through a communication network. In a distributed computing environment, program modules can be located in both local and remote memory storage devices.

Computing devices typically include a variety of media, which can include computer-readable storage media and / or communication media, the two terms of which are different from each other herein as follows: used. Computer-readable storage media can be any available storage medium that can be accessed by a computer, including both volatile and non-volatile media, removable and non-removable media. By way of example, but not limited to, computer readable storage media shall be implemented in connection with any method or technique for storing information such as computer readable instructions, program modules, structured or unstructured data. Can be done.

Computer-readable storage media include, but are not limited to, random access memory (RAM), read-only memory (ROM), electrically erasable programmable read-only memory (EEPROM), flash memory or other memory technology, and compact disk read-only memory. (CD-ROM), digital versatile disk (DVD) or other optical disk storage device, magnetic cassette, magnetic tape, magnetic disk storage device or other magnetic storage device, or can be used to store desired information. Other tangible and / or non-temporary media can be included. In this regard, the term "tangible" or "non-temporary" as applied herein to a storage device, memory or computer-readable medium excludes only the temporary propagating signal itself as a modifier. It should be understood that it does not waive any rights to any standard storage, memory or computer readable medium, not just the temporary propagating signal itself.

Computer-readable storage media shall be accessed by one or more local or remote computing devices, for example, via access requests, queries or other data retrieval protocols, for various actions relating to the information stored by the media. Can be done.

The communication medium usually embodies computer-readable instructions, data structures, program modules or other structured or unstructured data in data signals to be modulated, such as carrier waves or other transport mechanisms, and is arbitrary. Includes information delivery or transport media. The term "modulated data signal" or signal refers to a signal having one or more of the characteristics set or modified to encode information within one or more signals. By way of example, but not limited to, communication media include wired media such as wired networks or directly connected connections, and wireless media such as acoustic, RF, infrared and other wireless media.

Referring again to FIG. 26, whether signals are transmitted or received via at least a portion of a base station (eg, base station device 1504, macrocell site 1502, or base station 1614) or a central office (eg, central office 1501 or 1611). Or an environment example 2600 that forms at least a part of a base station or a central office. At least a part of the environment example 2600 can also be used for the transmission device 101 or 102. An example environment can include computer 2602, which includes processing unit 2604, system memory 2606, and system bus 2608. System bus 2608 combines system components including, but not limited to, system memory 2606 into processing unit 2604. The processing unit 2604 can be any of a variety of commercially available processors. Dual microprocessors and other multiprocessor architectures are also available as processing units 2604.

The system bus 2608 is of several types that can be further interconnected to a memory bus (with or without a memory controller), a peripheral bus and a local bus using any of a variety of commercially available bus architectures. Can be one of the bus structures of. The system memory 2606 includes a ROM 2610 and a RAM 2612. The basic input / output system (BIOS) can be stored in non-volatile memory such as ROM, erasable programmable read-only memory (EPROM), EEPROM, etc., and the BIOS transfers information between elements in the computer 2602 during startup, etc. Includes basic routines that facilitate doing. The RAM 2612 can also include a high speed RAM such as a static RAM for caching data.

The computer 2602 can also be configured for external use in a suitable chassis (not shown) with an internal hard disk drive (HDD) 2614 (eg EIDE, SATA) and a magnetic floppy disk drive (FDD) 2616 (eg). , For reading or writing to a removable diskette 2618) and an optical disk drive 2620 (for example, reading or writing a CD-ROM disc 2622, or for reading or writing to another high capacity optical medium such as a DVD). The hard disk drive 2614, the magnetic disk drive 2616, and the optical disk drive 2620 can be connected to the system bus 2608 by the hard disk drive interface 2624, the magnetic disk drive interface 2626, and the optical drive interface 2628, respectively. The interface 2624 for implementing an external drive includes at least one or both of the Universal Serial Bus (USB) and the Institute of Electrical and Electronics Engineers (IEEE) 1394 interface technology. Other external drive connection techniques are also within the scope of the considerations of the embodiments described herein.

The drive and its associated computer-readable storage medium provide non-volatile storage of data, data structures, computer-executable instructions, and the like. In the case of computer 2602, the drive and storage medium correspond to the storage of arbitrary data in a suitable digital format. The above description of computer-readable storage media refers to hard disk drives (HDDs), removable magnetic disks, and removable optical media such as CDs or DVDs, but can be read by computers such as zip drives, magnetic cassettes, flash memory cards, cartridges, etc. Other types of storage media can also be used in exemplary operating environments, and any such storage medium can include computer-executable instructions for performing the methods described herein. It will be understood by those in the art.

A plurality of program modules including the operating system 2630, one or more application programs 2632, other program modules 2634 and program data 2636 can be stored in the drive and RAM 2612. All or part of the operating system, applications, modules and / or data can also be cached in RAM 2612. The systems and methods described herein can be implemented utilizing various commercially available operating systems or combinations of operating systems. An example of an application program 2632 that can be implemented by processing unit 2604 or otherwise executed includes a diversity selection decision performed by transmitting device 101 or 102.

The user can enter commands and information into the computer 2602 through one or more wired / wireless input devices, such as a pointing device such as a keyboard 2638 and a mouse 2640. Other input devices (not shown) can include microphones, infrared (IR) remote controls, joysticks, gamepads, stylus pens, touch screens, and the like. These input devices and other input devices are often connected to the processing unit 2604 through an input device interface 2642 that can be coupled to the system bus 2608, but with a parallel port, an IEEE1394 serial port, a game port, and a universal serial. It can also be connected by other interfaces such as a bus (USB) port and IR interface.

A monitor 2644 or other type of display device can also be connected to the system bus 2608 via an interface such as a video adapter 2646. Also, in an alternative embodiment, the monitor 2644 presents any display device (eg, a display) for receiving display information associated with computer 2602 via any means of communication, including via the Internet and cloud-based networks. It will be understood that it can be another computer, a smartphone, a tablet computer, etc.). In addition to the monitor 2644, the computer typically includes other peripheral output devices (not shown) such as speakers and printers.

The computer 2602 can operate in a networked environment using a logical connection via wired and / or wireless communication with one or more remote computers such as the remote computer 2648. The remote computer 2648 can be a workstation, server computer, router, personal computer, portable computer, entertainment equipment with built-in microprocessor, peer device or other common network node, and usually many or all of the elements described for computer 2602. However, for brevity, only one memory / storage device 2650 is shown. The logical connections shown include wired / wireless connections to local area networks (LAN) 2652 and / or larger networks, such as wide area networks (WAN) 2654. Such LAN and WAN networking environments are common in offices and enterprises, all of which facilitate global communication networks, such as enterprise-scale computer networks such as intranets that can connect to the Internet.

When used in a LAN networked environment, the computer 2602 can connect to the local network 2652 through a wired and / or wireless communication network interface or adapter 2656. The adapter 2656 can facilitate wired or wireless communication with the LAN 2652, where the LAN can also include a wireless AP for communicating with the wireless adapter 2656.

When used in a WAN networked environment, the computer 2602 can include a modem 2658, can connect to a communication server on WAN 2654, or for establishing communication over WAN 2654, for example via the Internet. Have other means. The modem 2658 can be an internal or external and wired or wireless device and can be connected to the system bus 2608 via the input device interface 2642. In a networked environment, the program module illustrated for computer 2602 or a portion thereof can be stored in remote memory / storage device 2650. It will be appreciated that the network connection shown is an example and other means of establishing communication links between computers may be used.

The computer 2602 is associated with any wireless device or entity that is operationally arranged in wireless communication, such as a printer, scanner, desktop and / or portable computer, portable data assistant, communications satellite, wirelessly detectable tag. Alternatively, it can be made operational to communicate with any part of the location (eg, a kiosk, newsstand, dressing room), and a telephone. It can include wireless fidelity (Wi-Fi) and BLUETOOTH® wireless technology. In this way, communication can be a defined structure, as in the case of conventional networks, or simply ad hoc communication between at least two devices.

Wi-Fi allows you to connect to the Internet wirelessly from your chaise lounge at home, from your bed in your hotel room, or from your meeting room while you work. Wi-Fi is a wireless technology similar to that used in mobile phones, which allows such devices, such as computers, to send and receive data both indoors and outdoors within the range of a base station. Will be. Wi-Fi networks use a wireless technology called 802.11 (a, b, g, n, ac, ag, etc.) to provide secure, reliable, and fast wireless connectivity. Wi-Fi networks can be used to connect computers to each other, to the Internet, and to wired networks (IEEE802.3 or Ethernet® can be used). Wi-Fi networks are used in many offices because they operate, for example, in unlicensed 2.4 GHz and 5 GHz radio bands, or with products that include both bands (dual bands). It can provide real-world performance similar to a basic 10BaseT wired Ethernet network.

FIG. 27 presents an exemplary embodiment 2700 of a mobile network platform 2710 that can implement and utilize one or more aspects of the disclosed subject matter described herein. In one or more embodiments, the mobile network platform 2710 is disclosed as a base station (eg, base station device 1504, macrocell site 1502, or base station 1614), central office (eg, central office 1501 or 1611), or disclosed. Signals transmitted and received by the transmitting device 101 or 102 associated with the subject can be generated and received. In general, wireless network platforms 2710 include both packet-switched (PS) traffic (eg, Internet Protocol (IP), Frame Relay, asynchronous transport mode (ATM)) and circuit-switched (CS) traffic (eg, voice and data). It can also include components that facilitate control generation for networked wireless telecommunications, such as nodes, gateways, interfaces, servers or heterogeneous platforms. As a non-limiting example, the wireless network platform 2710 can be included within a telecommunications carrier network and can be considered a carrier-side component, as discussed elsewhere herein. The mobile network platform 2710 is received from a legacy network such as the telephone network 2740 (eg, the public switched telephone network (PSTN), or the public land mobile network (PLMN)), or the signaling system # 7 (SS7) network 2770. Includes a CS gateway node 2722 that can have an interface with CS traffic. Circuit-switched gateway node 2722 can allow and authenticate traffic (eg, voice) originating from such networks. Further, the CS gateway node 2722 can access mobility data or roaming data generated through SS7 network 2770, eg, mobility data stored in a visitor location register (VLR) that can reside in memory 2730. .. In addition, CS gateway node 2722 has CS-based traffic and signaling as well as an interface with PS gateway node 2718. As an example, in a 3GPP UMTS network, CS gateway node 2722 can be implemented at least partially in gateway GPRS support node (GGSN). It should be understood that the functions and specific operations of CS gateway node 2722, PS gateway node 2718 and serving node 2716 are provided and determined by the wireless technology utilized by the mobile network platform 2710 for telecommunications.

In addition to receiving and processing CS exchange traffic and signaling, PS Gateway Node 2718 can allow and authenticate PS-based data sessions with served mobile devices. Data sessions can include traffic or content that is exchanged with networks outside the wireless network platform 2710, such as Wide Area Network (WAN) 2750, Corporate Network 2770 and Service Network 2780, which are local area networks ( It can be embodied in LAN) and can be interface-connected with the mobile network platform 2710 through the PS gateway node 2718. It should be noted that WAN2750 and corporate network 2760 can at least partially embody service networks such as IP Multimedia Subsystem (IMS). Based on the wireless technology layer available in technical resource 2717, the packet-switched gateway node 2718 can generate a packet data protocol context when a data session is established and routes the packetized data. Other data structures that facilitate can also be generated. To that end, in one aspect, the PS gateway node 2718 can facilitate packetized communication with heterogeneous wireless networks such as Wi-Fi networks (eg, 3GPP UMTS networks (not shown)). Can include a tunnel termination gateway (TTG) in.

In embodiment 2700, the wireless network platform 2710 also includes a serving node 2716, which serves various packets of data streams received through the PS gateway node 2718 based on the available wireless technology layer within the technical resource 2717. Transport the converted flow. Note that in the case of the technical resource 2717, which relies primarily on CS communication, the server node can deliver traffic independently of the PS gateway node 2718. For example, a server node can at least partially embody a mobile exchange center. As an example, in a 3GPP UMTS network, the serving node 2716 can be embodied in a serving GPRS support node (SGSN).

For wireless technologies that utilize packetized communications, server 2714 within the wireless network platform 2710 creates multiple heterogeneous packetized data streams or flows and manages such flows (eg, scheduling). You can run many applications that can do, queue, format ...). Such applications can include add-on mechanisms for standard services provided by the wireless network platform 2710 (eg, provisioning, billing, customer support ...). A data stream (eg, content that is part of a voice call or data session) can be transported to the PS gateway node 2718 for authorization / authentication and initiation of the data session and then to the serving node 2716 for communication. Can be transported. In addition to the application server, the server 2714 can include a utility server, which can at least partially implement provisioning servers, operations and maintenance servers, certification authorities and firewalls, and other security mechanisms. It can include a security server, etc. In one aspect, the security server protects the communications served through the wireless network platform 2710, and in addition to the authorization and authentication procedures that CS gateway node 2722 and PS gateway node 2718 can specify, network operation and data integrity. To secure. In addition, the provisioning server can provision services from external networks, such as networks operated by heterogeneous service providers, such as WAN2750 or Global Positioning System (GPS) networks (not shown). The provisioning server is also associated with a wireless network platform 2710, such as the distributed antenna network shown in FIG. 1, which improves wireless service coverage by providing additional network coverage (eg, deployed and operated by the same service provider). Coverage can also be provisioned through the network. Repeater devices such as those shown in FIGS. 7, 8 and 9 also improve network coverage in order to improve the subscriber service experience with UE2775.

Note that server 2714 may include one or more processors configured to at least partially provide the functionality of macro network platform 2710. To that end, one or more processors can, for example, execute code instructions stored in memory 2730. It should be understood that server 2714 may include content manager 2715, which behaves substantially as described above.

In an exemplary embodiment 2700, the memory 2730 can store information related to the operation of the wireless network platform 2710. Other operational information includes provisioning information for mobile devices served through the wireless platform network 2710, subscriber databases; application intelligence, pricing schemes such as promotional fees, flat-rate programs, coupon distribution campaigns; heterogeneous wireless or wireless, technology. It can include technical specifications and the like that match the telecommunications protocol for layer operation. The memory 2730 can also store information from at least one of the telephone network 2740, WAN2750, corporate network 2770 or SS7 network 2760. In one aspect, the memory 2730 can be accessed, for example, as part of a datastore component or as a remotely connected memory store.

To provide a situation regarding the various aspects of the disclosed subject, FIG. 27 and the following studies provide a concise and general description of the appropriate environment in which the various aspects of the disclosed subject can be realized. Intended to do. The subject matter has been described in the general context of computer-executable instructions for computer programs running on one and / or multiple computers, but the disclosed subject matter is realized in combination with other program modules. It will be recognized by those skilled in the art. In general, a program module includes routines, programs, components, data structures, etc. that perform a particular task and / or realize a particular abstract data type.

FIG. 28 shows an exemplary embodiment of the communication device 2800. The communication device 2800 can serve as an exemplary embodiment of devices such as mobile devices and in-building devices referenced in the present disclosure (eg, in FIGS. 15, 16A, and 16B).

The communication device 2800 includes a wired and / or wireless transmitter / receiver 2802 (transmission / receiver 2802 in the present specification), a user interface (UI) 2804, a power supply 2814, a location receiver 2816, a motion sensor 2818, an orientation sensor 2820, and their operation. A controller 2806 to manage can be included. The transmitter / receiver 2802 can support short-range or long-range wireless access technologies such as Bluetooth®, ZigBee®, WiFi, DECT, or cellular communication technology, to name a few (Bluetooth (registered)). Trademarks) and ZigBee® are trademarks registered by Bluetooth® Special Interest Group and ZigBee® Alliance, respectively). Cellular technology can include, for example, CDMA-1X, UMTS / HSDPA, GSM / GPRS, TDMA / EDGE, EV / DO, WiMAX, SDR, LTE, and other next-generation wireless communication technologies being developed. The transmitter / receiver 2802 can also be configured to support circuit-switched wired access technology (PSTN, etc.), packet-switched wired access technology (TCP / IP, VoIP, etc.), and combinations thereof.

The UI2804 can include a pressable or touch-sensitive keypad 2808 having a navigation mechanism such as a rollerball, joystick, mouse, or navigation disc that controls the operation of the communication device 2800. The keypad 2808 may be an integral part of the housing assembly of the communication device 2800, or can be operated by a connected wired interface (such as a USB cable) or a wireless interface that supports, for example, Bluetooth®. It may be an independent device to be combined. The keypad 2808 can represent a QWERTY keypad with a numeric keypad and / or alphanumeric keys commonly used on telephones. The UI2804 can further include a display 2810 such as a monochrome or color LCD (liquid crystal display), an OLED (organic light emitting diode), or other suitable display technology that transmits an image to the end user of the communication device 2800. In one embodiment where the display 2810 is touch sensitive, some or all of the keypad 2808 can be presented by the display 2810 having a navigation function.

The display 2810 can also serve as a user interface for detecting user input using touch screen technology. As a touch screen display, the communication device 2800 can be configured to present a user interface with a graphical user interface (GUI) element that can be selected by the user with the touch of a finger. The touch screen display 2810 can include capacitive, resistance, or other form of detection technology in which the user's finger detects the amount of surface area placed on a portion of the touch screen display. This detection information can be used to control the operation of GUI elements or other functions of the user interface. The display 2810 may be an integral part of the housing assembly of the communication device 2800, or it may be an independent device communicatively coupled to it by a connected wired interface (cable or the like) or a wireless interface.

The UI2804 can also include an audio system 2812 that utilizes audio technology to transmit low volume audio (such as audio heard near the human ear) and high volume audio (such as a hands-free speakerphone). The audio system 2812 may further include a microphone that receives the end user's audible signal. The audio system 2812 can also be used for voice recognition applications. The UI2804 can further include an image sensor 2813 such as a charge-coupled device (CCD) camera that captures a still image or moving image.

The power supply 2814 uses common power management techniques such as replaceable and rechargeable batteries, supply control techniques, and / or charging system technology to power the components of the communication device 2800 over long distances or near. Distance portable communication can be facilitated. Alternatively or in combination, the charging system can utilize an external power source such as DC power supplied via a physical interface such as a USB port or other suitable tethering technology.

The location receiver 2816 can identify the location of the communication device 2800 based on a signal generated by a group of GPS satellites by using a positioning technology such as an assisted GPS compatible Global Positioning System (GPS) receiver. The location can be used to promote location services such as navigation. The motion sensor 2818 can detect motion of the communication device 2800 in three-dimensional space using motion detection techniques such as accelerometers, gyroscopes, or other suitable motion detection techniques. The orientation sensor 2820 uses orientation detection technology such as a magnetometer to detect the orientation of the communication device 2800 (north, south, west, and east, as well as orientation combined with degrees, minutes, or other suitable orientation scale). can do.

The communication device 2800 uses a transmitter / receiver 2802 to perform cellular, WiFi, Bluetooth (registration) by means of detection techniques such as the use of received signal strength indicator (RSSI) and / or signal arrival time (TOA) or flight time (TOF) measurements. It can also identify proximity to a trademark) or other wireless access point. Controller 2806, along with related storage memory such as flash, ROM, RAM, SRAM, DRAM, or other storage technology, is a microprocessor, digital signal processor (DSP), programmable gate array, application-specific integrated circuit, and / or A computing technique such as a video processor can be used to execute computer instructions, control the components of the communication device 2800, and process the data supplied by the components of the communication device 2800.

In one or more embodiments of the present disclosure, other components not shown in FIG. 28 can be used. For example, the communication device 2800 may include a slot for adding or removing identification modules such as a subscriber identification module (SIM) card or a general purpose integrated circuit card (UICC). The SIM or UICC card can be used for identifying subscriber services, executing programs, storing subscriber data, and the like.

In the present specification, the terms "store", "storage", "data store", "data storage device", "database", and any other information storage component related to the operation and function of the component are referred to as "memory". Refers to an entity or a component containing memory embodied in "component" and "memory". The memory components described herein can be either volatile or non-volatile memory, or can include both volatile and non-volatile memory, by way of example but not limited to. It will be appreciated that it may include volatile memory, non-volatile memory, disk storage and memory storage. Further, a read-only memory (ROM), a programmable ROM (PROM), an electrically programmable ROM (EPROM), an electrically erasable ROM (EEPROM), or a flash memory may include a non-volatile memory. Volatile memory can include random access memory (RAM) that acts as external cache memory. By way of example, but not limited to, RAMs include synchronous RAM (SRAM), dynamic RAM (DRAM), synchronous DRAM (SDRAM), double data rate SDRAM (DDR SDRAM), enhanced SDRAM (ESRAM), Synclink DRAM (SLRAM) and It is available in many forms such as direct RambusRAM (DRRAM). Furthermore, the memory components disclosed in the systems or methods herein are intended to include, but are not limited to, these and any other suitable type of memory.

Further disclosed subjects are single-processor or multi-processor computer systems, mini-computing devices, main-frame computers, as well as personal computers, handheld computing devices (eg, PDA, telephones, smartphones, watches, tablet computers, netbook computers). Etc.), it should be noted that it can be practiced in other computer system configurations including microprocessor-based or programmable home appliances or industrial electronic devices. The illustrated embodiment can also be practiced in a distributed computing environment in which tasks are performed by remote processing devices linked through a communication network. However, some, but not all, aspects of this disclosure can be practiced on a stand-alone computer. In a distributed computing environment, program modules can be located within both local and remote memory storage devices.

Some of the embodiments described herein can also utilize artificial intelligence (AI) to facilitate the automation of one or more features described herein. For example, artificial intelligence can be used in the optional training controller 230 to evaluate and select candidate frequencies, modulation schemes, MIMO modes, and / or waveguide modes to maximize transfer efficiency. Multiple embodiments (eg, related to automatically identifying the acquired cell site that offers the greatest value / benefit after being added to an existing communication network) have AI to perform the various embodiments. Various methods based on can be used. In addition, classifiers can be used to determine the ranking or prioritization of each cell site in the acquisition network. The classifier is a function that maps the input attribute vector x = (x1, x2, x3, x4, ..., xn) to the confidence that the input belongs to one class, that is, f (x) = confidence. Degree (class). Such classification is a probabilistic analysis and / or a statistical analysis (eg, taking into account the usefulness and cost of the analysis) to predict or infer the behavior that the user wants to be performed automatically. Can be used. A support vector machine (SVM) is an example of a classifier available. The SVM works by finding a hypersurface in the space of possible inputs, which attempts to separate the trigger criteria from non-trigger events. Intuitively, this makes the classification accurate to test data that is close to training data, but not identical. Other directed and undirected model classification techniques include, for example, naive Bayesian networks, Bayesian networks, decision trees, neural networks, fuzzy logic models, and stochastic classification models that provide different independent patterns are available. As used herein, classification also includes statistical regression used to develop models of priority.

As will be readily appreciated, one or more of the embodiments will be implicitly trained (eg, by observing UE behavior, receiving operator preferences, historical information, external information). ), As well as a classifier that is clearly trained (eg, with general training data) is available. For example, the SVM can be configured via a learning or training stage within the classifier constructor and feature selection module. Therefore, using a classifier, but not limited to, any of the acquired cell sites will benefit the maximum number of subscribers, and / or of the acquired cell sites, according to predetermined criteria. Multiple functions can be automatically learned and executed, including determining which of the acquired cell sites will add a minimum value to the existing communication network coverage.

As used in some contexts in this application, in some embodiments, terms such as "component", "system", etc. can be used with a computer-related entity, or one or more specific functions. It is intended to refer to or include an entity associated with a device, which entity can be either hardware, a combination of hardware and software, software or running software. As an example, components can be, but are not limited to, processes, processors, objects, executables, threads of execution, computer executable instructions, programs and / or computers running on the processor. By way of example, but not limited to, both an application running on a server and a server can be components. One or more components may reside within a thread of process and / or execution, and the components may be localized on one computer and / or distributed among two or more computers. is there. In addition, these components can be run from different computer-readable media with different data structures stored in it. A component interacts with another system over a signal, for example, over one or more data packets (data from a component that interacts with another component in a local system, a distributed system, and / or a network such as the Internet. It is possible to communicate via local and / or remote processes according to the signal having the data). As another example, a component can be a device having a particular function provided by a mechanical component operated by an electrical or electronic circuit operated by a software or firmware application performed by the processor, the processor being the device. It can be inside or outside of and runs at least part of a software or firmware application. As yet another example, a component can be a device that provides a particular function through an electronic component without the use of mechanical parts, and the electronic component runs software or firmware that at least partially provides the functionality of the electronic component. Therefore, the processor can be included in it. Although various components have been exemplified as separate components, it is possible to realize multiple components as a single component or a single component as multiple components without departing from the exemplary embodiment. Will be understood.

In addition, various embodiments use standard programming and / or engineering techniques to create software, firmware, hardware, or any combination thereof that controls a computer to achieve the disclosed subject matter. , Method, device or product. As used herein, the term "product" is intended to include any computer-readable device, or computer program accessible from a computer-readable storage / communication medium. For example, computer-readable storage media include, but are not limited to, magnetic storage devices (eg, hard disks, floppy disks, magnetic strips), optical disks (eg, compact discs (CDs), digital versatile discs (DVDs)), smart cards and It can include flash memory devices (eg, cards, sticks, key drives). It will be appreciated by those skilled in the art that, of course, many modifications to this configuration can be made without departing from the scope or intent of the various embodiments.

In addition, the terms "example" and "exemplary" are used herein to mean serve as an example or example. Any embodiment or design described herein as "example" or "exemplary" should not necessarily be construed as preferred or advantageous over other embodiments or designs. Rather, the use of the word example or exemplary is intended to present the concept concretely. As used in this application, the term "or" is intended to mean an inclusive "or" rather than an exclusive "or". That is, unless otherwise indicated, or unless otherwise apparent in the context, "X utilizes A or B" is intended to mean any of the natural inclusive permutations. That is, when X uses A, X uses B, or X uses both A and B, "X uses A or B" under any of the above cases. To do "is satisfied. Furthermore, the articles "one (a)" and "one (an)" used in the present application and the appended claims are generally intended to be in the singular or unless otherwise indicated. It should be construed to mean "one or more" unless it is clear from.

In addition, it represents terms (and / or similar terminology) such as "user device", "mobile station", "mobile subscriber station", "access terminal", "terminal", "handset", "mobile device". Terminology) refers to a wireless device used by a subscriber or user of a wireless communication service to receive or carry data, control, voice, video, sound, games or virtually any data or signaling stream. be able to. The above terms are used interchangeably herein and with reference to the relevant drawings.

Moreover, terms such as "user," "subscriber," "customer," and "consumer" are used interchangeably throughout, unless certain differences between the terms are justified in the context. Such terms are supported through real human beings, or artificial intelligence (eg, the ability to reason at least based on complex mathematical forms) that can provide simulated visual, speech recognition, etc. It should be understood that it can refer to automated components.

As used herein, the term "processor" is used, but is not limited to, a single core processor, a single processor capable of software multithread execution, a multicore processor, a multicore processor capable of software multithread execution, and a hardware multi. It can refer to virtually any computing unit or device, including multi-core processors using threading technology, parallel platforms, and parallel platforms with distributed shared memory. In addition, the processors include integrated circuits, application specific integrated circuits (ASICs), digital signal processors (DSPs), field programmable gate arrays (FPGAs), programmable logic controllers (PLCs), complex programmable logic devices (CPLDs), discrete gates or It can refer to transistor logic, discrete hardware components, or any combination thereof designed to perform the functions described herein. Processors can utilize nanoscale architectures such as transistors, switches and gates based on molecules or quantum dots to optimize the spatial utilization of user equipment or improve performance. The processor can also be realized as a combination of computing processing units.

As used herein, terms such as "data storage", "data storage", "database", and virtually any other information storage component related to the operation and function of the component are "memory". Refers to an entity embodied in "component" or "memory", or a component containing memory. It will be appreciated that the memory components or computer-readable storage media described herein can be either volatile or non-volatile memory, or can include both volatile and non-volatile memory.

What has been described so far includes mere examples of various embodiments. Of course, no possible combination of components or methods can be described to illustrate these examples, and one of ordinary skill in the art will be able to make many further combinations and substitutions of this embodiment. You can recognize that. Accordingly, the embodiments disclosed and / or claimed herein are intended to include all such modifications, modifications and variants that fall within the spirit and scope of the appended claims. doing. Moreover, as long as the term "includes" is used either in the detailed description or in the claims, such term is used as a transitional term in the claims. It is intended to be as comprehensive as it is sometimes interpreted.

In addition, the flow chart may include a "start" and / or "continue" indication. The "start" and "continue" indications indicate that the presented steps can be optionally incorporated into other routines or used in conjunction with other routines. In this regard, "start" indicates the beginning of the first step presented and may be preceded by other activities not specifically illustrated. In addition, the "continuation" indication indicates that the presented step may be performed multiple times and / or may be taken over by an activity not specifically shown. Moreover, although the flow diagram shows a particular order of steps, other orders are possible as long as the principle of causality is maintained.

Also, as used herein, the terms "operably combined to", "combined to", and / or "combined" are direct combinations between items. And / or includes indirect binding between items via one or more intervening items. Such items and intervening items include, but are not limited to, junctions, communication paths, components, circuit elements, circuits, functional blocks and / or devices. As an example of indirect coupling, the data carried from the first item to the second item is modified by one or more intervening items by changing the form, nature or format of the information in the signal. However, nevertheless, one or more information elements in the signal are carried so that the second item can recognize them. In a further example of indirect binding, the action on the first item can cause a reaction on the second item as a result of the action and / or reaction within one or more intervening items.

Although specific embodiments have been shown and described herein, it should be understood that any configuration that achieves the same or similar objectives may replace the embodiments described or shown herein. The present disclosure is intended to include any conforming or modified form of various embodiments. A combination of the above embodiments and other embodiments not specifically described herein can be used in the present disclosure. For example, one or more features from one or more embodiments can be combined with one or more features of one or more other embodiments. Features that are positively described in one or more embodiments are negatively described in the embodiments and excluded from the embodiments, with or without substitutions in other structural and / or functional features. It may be done. The steps or functions described with respect to the embodiments of the present disclosure can be performed in any order. The steps or functions described with respect to embodiments of the present disclosure may be performed alone or in combination with other steps or functions of the present disclosure, and other practices not described in the present disclosure. It may be performed from the form or other steps. Moreover, more or less than all of the features described for one embodiment may be utilized.

Claims (10)

Receiving multiple communication signals and
The transmitting device comprises generating a plurality of wireless signals according to the plurality of communication signals to induce a plurality of electromagnetic waves at least partially coupled to a dielectric layer environmentally formed on a non-insulated conductor.
The dielectric layer includes an aluminum oxide layer, and the plurality of electromagnetic waves propagate along the dielectric layer of the non-insulating conductor without the need for an electrical feedback path.
Each electromagnetic wave of the plurality of electromagnetic waves transmits at least a part of the plurality of communication signals.
The plurality of electromagnetic waves have a plurality of wave modes including a first hybrid wave mode and a second hybrid wave mode.
The first electromagnetic wave of the plurality of electromagnetic waves has the first hybrid wave mode including the first target polarity.
The second electromagnetic wave of the plurality of electromagnetic waves has the second hybrid wave mode including the second target polarity.
The first target polarity is substantially orthogonal to the second target polarity.
The first target polarity and the second target polarity reduce interference between at least the plurality of electromagnetic waves, and the receiving device extracts at least the portion of the plurality of communication signals from each electromagnetic wave of the plurality of electromagnetic waves. The way to enable. The method of claim 1, wherein one of the plurality of wave modes comprises a fundamental wave mode, and another mode of the plurality of wave modes comprises a non-basic wave mode. The method of claim 1, wherein the first hybrid wave mode includes a HE11 wave mode. The method according to claim 1, wherein the plurality of wave modes further include a fundamental wave mode. The method of claim 4, wherein the fundamental wave mode, the first hybrid wave mode, and the second hybrid wave mode are substantially orthogonal to each other. The first portion of the plurality of electromagnetic waves operates in the first frequency band, the second portion of the plurality of electromagnetic waves operates in the second frequency band, and the first frequency band operates in the first frequency band. The method according to claim 1, which is different from the frequency band of 2. The method of claim 1, wherein the plurality of wave modes are substantially orthogonal to each other, thereby promoting wave mode division multiplexing. The method of claim 1, wherein the plurality of electromagnetic waves are configured for frequency division multiplexing. Detecting obstacles that cause propagation loss affecting at least one of the plurality of electromagnetic waves.
The method of claim 1, further comprising adjusting at least one of the plurality of electromagnetic waves to at least reduce the propagation loss. The method of claim 9, wherein the obstacle comprises water.