JP6394823B2 - Power converter - Google Patents

Description

  The present invention relates to a power conversion device including a snubber circuit.

  Patent Document 1 discloses a snubber circuit that suppresses spike voltage. The snubber circuit described in Patent Document 1 includes a series circuit of a diode and a capacitor provided on the secondary side of the transformer of the switching regulator, and a switch element that discharges the charging voltage of the capacitor. The snubber circuit charges the generated spike voltage to the capacitor and immediately turns on the switch element to discharge the charge voltage as part of the output voltage. The power conversion efficiency is improved by regenerating the spike voltage stored in the capacitor without being consumed by the snubber circuit.

  Incidentally, as a switching regulator using a transformer, for example, there is a DC-DC converter. In this DC-DC converter, depending on the circuit system on the primary side of the transformer, a system that full-wave rectifies the current output from the transformer may be employed. For example, this is a case where a circuit system such as a full bridge, a half bridge, or a push-pull is adopted on the primary side of the transformer. In addition, as a full-wave rectification method, there are a bridge rectification method and an intermediate tap method, but depending on the required characteristics (for example, reduction of conduction loss), a method of full-wave rectifying the current output from the transformer by the intermediate tap method May be adopted. An example in which the intermediate tap method is employed is Patent Document 2 and the like.

JP-A-1-202161 JP 58-175972 A

  The snubber circuit described in Patent Document 1 and the DC-DC converter described in Patent Document 2 can prevent a decrease in power conversion efficiency. However, when the snubber circuit described in Patent Document 1 is applied to the DC-DC converter described in Patent Document 2, the following problems occur. In the center tap type rectifier circuit, the voltage cycle on the secondary side is ½ of the switching cycle on the primary side. For this reason, if the snubber circuit described in Patent Document 1 is simply applied to the DC-DC converter described in Patent Document 2, the switch element of the snubber circuit is turned on even during the ON period of the rectifying switch to be protected. Period occurs, and excessive power stress is applied to the snubber circuit. As a result, the snubber circuit may be damaged or overheating may occur.

  Accordingly, an object of the present invention is to provide a power conversion device including a snubber circuit and a center tap type rectifier circuit, in which the power stress of the snubber circuit connected to the rectifying switch element is suppressed. is there.

  The power conversion device according to the present invention includes a transformer having a primary winding to which an AC voltage is applied, a secondary winding including a first end, a second end, and a center tap, the first end, and the first end. A first switch element connected between the output section, a second switch element connected between the second end and the first output section, and between the center tap and the second output section. A snubber circuit having a connected choke coil, a third switch element and a capacitor connected in series, and connected in parallel to at least one of the first switch element and the second switch element; and the third switch element A control circuit for turning on and off, the control circuit having a series circuit of a transformer auxiliary winding magnetically coupled to the primary winding of the transformer and a coil coupling winding magnetically coupled to the choke coil. And the series A path is connected between the control terminal of the third switch element and the first end of the secondary winding, and the center tap and the second of the secondary winding and the secondary winding. A winding ratio between one end of the winding portion between one end or the winding portion between the center tap and the second end and the transformer auxiliary winding is represented by N1: N2: N3, When the turns ratio of the choke coil and the coil coupling winding is expressed as N4: N5, and m = N5 / N4, n = N2 / N1, and n1 = N3 / N1, mn−n1 = 0 is satisfied. It is characterized by.

  According to this configuration, the third switch element is turned on only when the first switch element or the second switch element that is the rectifying switch element to be protected is turned off. Therefore, it is possible to suppress an excessive power stress from being applied to the snubber circuit, particularly the third switch element. Further, it is possible to reduce the spike voltage generated in the rectifying switch element to be protected by the snubber circuit while preventing the third switch element from being damaged.

  The series circuit further includes a second capacitor, and the power converter further includes a resistance element connected between the control terminal of the third switch element and the first end of the secondary winding. A differential circuit may be formed by the second capacitor and the resistance element.

  In this configuration, the ON period of the third switch element can be adjusted by the differentiating circuit. Thereby, it is possible to prevent the third switch element from being turned on during the on period of the first switch element or the second switch element provided with the snubber circuit. As a result, the discharge current from the capacitor during the ON period of the first switch element or the second switch element can be prevented.

  The power converter may include a diode having a cathode connected to the control terminal of the third switch element and an anode connected to a reference potential terminal of the third switch element.

  With this configuration, it is possible to prevent an excessive reverse voltage from being applied to the control terminal of the third switch element.

  The power converter includes: a fourth switch element connected between a control terminal of the third switch element and a reference potential terminal; and the fourth switch with a set time constant when the third switch element is turned on. And a time constant circuit for turning on the element, and the third switch element may be turned off when the fourth switch element is turned on.

  In this configuration, by turning on the fourth switch element, the charge of the control terminal of the third switch element can be extracted, and the third switch element can be turned off at higher speed. As a result, it is possible to prevent a discharge current from the capacitor due to the third switch element being turned on during the on period of the first switch element or the second switch element provided with the snubber circuit.

  According to the present invention, it is possible to prevent an excessive power stress from being applied to the snubber circuit even when a center tap type transformer is used. As a result, it is possible to suppress the snubber circuit from being damaged or causing overheating.

FIG. 1 is a circuit diagram of the power conversion apparatus according to the first embodiment. FIG. 2 is a diagram illustrating waveforms of the voltage across the coil, the voltage across the auxiliary winding, and the total voltage thereof. FIG. 3 is a diagram illustrating waveforms of the voltage across the auxiliary winding, the charging voltage of the capacitor, the drain-source voltage of the switching element, and the gate voltage of the snubber switch. FIG. 4 is a circuit diagram of the power conversion apparatus according to the second embodiment. FIG. 5 is a diagram showing waveforms of the gate voltage of the snubber switch, the charging voltage of the capacitor, the drain-source voltage of the switching element, the total voltage, and the voltage across the auxiliary winding. FIG. 6 is a circuit diagram of the power conversion apparatus according to the third embodiment. FIG. 7 is a diagram illustrating waveforms of the voltage across the auxiliary winding, the charging voltage of the capacitor, and the gate voltage of the snubber switch. FIG. 8A and FIG. 8B are diagrams illustrating a discharge circuit. 9A and 9B are diagrams illustrating a discharge circuit. FIG. 10 is a diagram showing waveforms of the voltage across the auxiliary winding, the charging voltage of the capacitor, and the gate voltage of the snubber switch. FIG. 11 is a circuit diagram of the power conversion apparatus according to the fifth embodiment.

(Embodiment 1)
FIG. 1 is a circuit diagram of a power conversion device 1 according to the first embodiment. The power converter 1 is a DC-DC converter provided with a center tap type rectifier circuit. The power conversion apparatus 1 includes input units IN1 and IN2 that input a DC voltage Vin and output units OUT1 and OUT2 that output a DC voltage Vout. The output unit OUT1 corresponds to a “first output unit” according to the present invention, and the output unit OUT2 corresponds to a “second output unit” according to the present invention.

  A switching circuit is connected to the input sections IN1 and IN2. The switching circuit is configured by connecting a series circuit of switching elements Q11 and Q12 and a series circuit of switching elements Q21 and Q22 in parallel. This switching circuit is switching-controlled by a driver (not shown), and switching elements Q11 and Q22 and switching elements Q12 and Q21 are alternately turned on and off. In FIG. 1, the switching elements Q11, Q12, Q21, and Q22 are MOSFETs, but may be elements having other structures such as IGBTs.

  The primary winding n11 of the transformer T1 is connected between the connection point of the switching elements Q11 and Q12 and the connection point of the switching elements Q21 and Q22. The secondary winding of the transformer T1 is configured by connecting a first winding n21 and a second winding n22 in series. A connection point P between the first winding n21 and the second winding n22 is a center tap of the secondary winding.

  The connection point P is connected to the output part OUT2 via the choke coil L1. The choke coil L1 is a primary winding of the transformer T2. One end of the first winding n21 opposite to the connection point P (corresponding to the “first end” in the present invention) is connected to the output part OUT1 via the switching element Q31. One end of the second winding n22 opposite to the connection point P (corresponding to the “second end” in the present invention) is connected to the output part OUT1 via the switching element Q32. A smoothing capacitor Co is connected between the output parts OUT1 and OUT2.

  Switching elements Q31 and Q32 are MOSFETs. Switching element Q31 is turned on / off in synchronization with on / off of switching elements Q12, Q21. Switching element Q32 is turned on / off in synchronization with on / off of switching elements Q11, Q22. The switching element Q31 corresponds to a “first switch element” according to the present invention. The switching element Q32 corresponds to a “second switch element” according to the present invention.

  When the switching elements Q11, Q22, and Q32 are on and the switching elements Q12, Q21, and Q31 are off (hereinafter, this state is referred to as a first state), the power conversion device 1 has a path indicated by a solid arrow shown in FIG. Current flows. When the switching elements Q11, Q22, and Q32 are off and the switching elements Q12, Q21, and Q31 are on (hereinafter, this state is referred to as a second state), the power conversion device 1 has a broken-line arrow shown in FIG. Current flows through the path.

  A snubber circuit 10 is connected in parallel to the switching element Q31. The snubber circuit 10 is a protection circuit that absorbs a spike voltage generated when the switching element Q31 is turned off and protects the switching element Q31 and surrounding components. The snubber circuit 10 is a series circuit of a snubber switch 11 and a capacitor 12.

  The snubber switch 11 is a MOSFET, the source of the snubber switch 11 is connected to the drain of the switching element Q31, and the drain of the snubber switch 11 is connected to the source of the switching element Q31 via the capacitor 12. The snubber switch 11 corresponds to a “third switch element” according to the present invention.

  A control circuit, which will be described later, is connected to the gate (control terminal) of the snubber switch 11 and is turned on and off by the control circuit. The snubber switch 11 is turned on during the off period of the switching element Q31 and is turned off during the on period of the switching element Q31. When the switching element Q31 is turned off, the voltage across the switching element Q31 rises rapidly. That is, a spike voltage is generated. At this time, when the snubber switch 11 is turned on, the spike voltage is absorbed (charged) in the capacitor 12. As a result, the switching element Q31 and its peripheral components can be prevented from being damaged by the spike voltage.

  The control circuit is a series circuit of the coil L2 and the auxiliary winding n23. This series circuit is connected between the gate and source of the snubber switch 11. The control circuit in the present embodiment corresponds to a “control circuit” according to the present invention. The capacitor C1 is a capacitor for adjusting the voltage between the gate and the source of the snubber switch 11.

  The coil L2 is a secondary winding of the transformer T2, and is magnetically coupled to the choke coil L1 of the primary winding. In either case of the first state or the second state, the current flowing through the choke coil L1 is in the same direction. For this reason, the polarity of the voltage induced in the coil L2 magnetically coupled to the choke coil L1 is the same. The coil L2 corresponds to a “coil coupling winding” according to the present invention.

  The auxiliary winding n23 of the control circuit is magnetically coupled to the primary winding n11 of the transformer T1. An AC voltage is applied to the primary winding n11 by switching of the switching circuit. For this reason, the polarity of the voltage induced in the auxiliary winding n23 is alternately inverted. In the case of the first state, the polarity of the voltage induced in the auxiliary winding n23 is the same as the polarity of the voltage induced in the coil L2. In the second state, the polarity of the voltage induced in the auxiliary winding n23 is opposite to the polarity of the voltage induced in the coil L2. The auxiliary winding n23 corresponds to a “transformer auxiliary winding” according to the present invention.

  The control circuit outputs a total voltage (V1 + V2) of the voltage V1 induced in the coil L2 and the voltage V2 induced in the auxiliary winding n23. This total voltage (V1 + V2) is applied to the gate of the snubber switch 11.

  The total voltage (V1 + V2) output from the control circuit has a rectangular wave shape that turns on the snubber switch 11 when the switching element Q31 is off and turns off the snubber switch 11 when the switching element Q31 is on. Each element of the power converter 1 is set to a constant.

  Here, the turns ratio of the primary winding n11, the first winding n21, and the auxiliary winding n23 is represented by N1: N2: N3, and the turns ratio of the choke coil L1 and the coil L2 is represented by N4: N5. . Further, m = N5 / N4, n = N2 / N1, and n1 = N3 / N1. In this case, when the condition of mn−n1 = 0 is satisfied, the snubber switch 11 is turned off when the switching element Q31 is turned on and turned on when the switching element Q31 is turned off. The reason will be described below.

  FIG. 2 is a diagram showing waveforms of the voltage V1 across the coil L2, the voltage V2 across the auxiliary winding n23, and the total voltage (V1 + V2) thereof.

  When the voltage across the choke coil L1 is represented by VL1, VL1 = n * Vin−Vout. The voltage V1 across the coil L2 magnetically coupled to the choke coil L1 is V1 = m * VL1 = m (n * Vin−Vout). If the switching period of the switching circuit on the primary side of the transformer T1 is represented by T, the repetition period of V1 is T / 2. The voltage V2 across the auxiliary winding n23 is V2 = n1 * Vin. The repetition period of V2 is a switching period T.

  The total voltage (V1 + V2) is expressed by the following formula (1).

V1 + V2 = m (n * Vin−Vout) + (− n1 * Vin)
= (Mn-n1) Vin-m * Vout (1)
In the periods (A) and (C) shown in FIG. 2, V2 = 0. That is, Vin = 0. In this case, V1 = −m * Vout. From the formula (1), V1 + V2 = −m * Vout.

  In the period (B) of FIG. 2, the total voltage (V1 + V2) becomes the same potential as the total voltage (V1 + V2) in the periods (A) and (C). It becomes a pulse voltage. In the formula (1), as described above, mn−n1 = 0 in the present invention, so that V1 + V2 = −m * Vout. That is, the total voltage (V1 + V2) in the periods (A), (B), and (C) is −m * Vout, which is the same potential. The total voltage (V1 + V2) is applied to the gate of the snubber switch 11, so that the snubber switch 11 is turned on / off in a cycle T.

  Here, it is assumed that the auxiliary winding n23 of FIG. 1 is not provided. In this case, the voltage output from the control circuit is only the voltage V1 across the coil L2. A voltage V 1 is applied to the gate of the snubber switch 11. Since the cycle of the voltage V1 is T / 2, the snubber switch 11 is turned on / off at a cycle of T / 2. Since the cycle of the switching element Q31 is T, the timing when the snubber switch 11 is turned on occurs when the switching element Q31 is turned on. In this case, the electric charge of the capacitor 12 is discharged through the switching element Q31, and power stress is applied to the snubber switch 11 and the capacitor 12.

  In the present embodiment, by providing the above-described configuration such as providing the auxiliary winding n23, power stress applied to the snubber circuit 10, particularly the snubber switch 11, can be suppressed, and the snubber circuit 10 can be prevented from being damaged and overheated.

  In the present invention, “mn−n1 = 0” is set. However, for example, when there is an error or variation due to a manufacturing error or component variation, mn−n1 is completely zero. In this case, mn−n1≈0 is sufficient. That is, it is only necessary to substantially satisfy “mn−n1 = 0”.

  FIG. 3 is a diagram illustrating waveforms of the voltage V2 across the auxiliary winding n23, the charging voltage V12 of the capacitor 12, the drain-source voltage Vds of the switching element Q31, and the gate voltage Vgs of the snubber switch 11. The periods (A), (B), and (C) shown in FIG. 3 are the same as the periods (A), (B), and (C) shown in FIG.

  As shown in FIG. 3, the gate voltage Vgs is applied to the snubber switch 11 and the capacitor 12 is charged with a spike voltage at the timing when the switching element Q31 is turned off. Then, when the snubber switch 11 is turned off when the switching element Q31 is turned on, the loss of electric charge (discharge) of the capacitor 12 can be reduced. In the present embodiment, since a slight delay occurs between the turn-on of the switching element Q31 and the turn-off of the snubber switch 11, the charging voltage V12 of the capacitor 12 shown in FIG.

  Thus, in this embodiment, the snubber switch 11 can be prevented from being damaged by making the on / off cycle of the snubber switch 11 the same as the switching cycle on the primary side of the transformer T1.

(Embodiment 2)
FIG. 4 is a circuit diagram of the power conversion device 2 according to the second embodiment. In this example, the power conversion device 2 is different from the first embodiment in that it includes a differentiation circuit.

  A resistor R <b> 1 is connected between the gate and source of the snubber switch 11. A differential circuit is configured by the resistor R1 and the capacitor C1. This differentiation circuit adjusts the on period of the snubber switch 11 by changing the pulsed gate voltage applied to the snubber switch 11. The differentiation circuit is set to a constant so that the on period of the snubber switch 11 is shorter than the off period of the switching element Q31.

  FIG. 5 is a diagram showing waveforms of the gate voltage Vgs of the snubber switch 11, the charging voltage V12 of the capacitor 12, the drain-source voltage Vds of the switching element Q31, the total voltage (V1 + V2), and the voltage V2 across the auxiliary winding n23. It is.

  By providing a differential circuit on the input side of the control terminal (gate) of the snubber switch 11, the waveform of the gate voltage Vgs applied to the snubber switch 11 gradually decreases after rising. For this reason, the on period of the snubber switch 11 is shorter than when the pulsed gate voltage Vgs is applied. As a result, the on period of the snubber switch 11 is shorter than the off period of the switching element Q31. Thus, it is possible to reliably prevent a period in which the snubber switch 11 is turned on during the on period of the switching element Q31 and the charging voltage of the capacitor 12 is discharged. Therefore, as shown in FIG. 5, the charging voltage V12 of the capacitor 12 is substantially constant.

  Thus, in the present embodiment, the snubber circuit 10 can be appropriately protected by preventing the capacitor 12 from discharging and flowing a large current.

(Embodiment 3)
FIG. 6 is a circuit diagram of the power conversion device 3 according to the third embodiment.

  This example is different from the second embodiment in that a diode D1 is connected in parallel to the resistor R1 of the power conversion device 2 according to the second embodiment. The anode of the diode D1 is connected to the source (reference potential terminal) of the snubber switch 11, and the cathode is connected to the gate of the snubber switch 11.

  As shown in FIG. 5 of the second embodiment, there is a timing when the gate voltage Vgs becomes a negative voltage by providing a differentiating circuit. When a negative gate voltage is applied to the snubber switch 11 that is a MOSFET, the breakdown voltage between the drain and the source (the maximum voltage that can be applied between the drain and the source) decreases. In the present embodiment, by providing the diode D1, the negative gate voltage Vgs is suppressed to be equal to or lower than the forward voltage of the diode D1.

  FIG. 7 is a diagram showing waveforms of the voltage V2 across the auxiliary winding n23, the charging voltage V12 of the capacitor 12, and the gate voltage Vgs of the snubber switch 11.

  The gate voltage Vgs shown in FIG. 5 has almost the same positive and negative absolute values. On the other hand, in the present embodiment, the absolute value of the negative gate voltage Vgs is lower than the positive gate voltage Vgs, and the negative gate voltage Vgs decreases almost only to the forward voltage (−Vf).

  Thus, by providing the diode D1 between the gate and the source of the snubber switch 11, it is possible to prevent an excessively negative gate voltage from being applied to the snubber switch 11.

(Embodiment 4)
This embodiment is different from the third embodiment in that a discharge circuit for discharging the gate charge of the snubber switch 11 and turning off the snubber switch 11 at higher speed is provided.

  8A, 8B, 9A, and 9B are diagrams illustrating a discharge circuit.

  The discharge circuit shown in FIG. 8A includes a resistor R2, a capacitor C2, and a switching element Q4. The switching element Q4 is a MOSFET having a drain connected to the gate of the snubber switch 11 and a source connected to the source of the snubber switch 11. The circuit of the resistor R1 and the capacitor C2 is a time constant circuit, and its connection point is connected to the gate of the switching element Q4. The resistor R2 is a discharging resistor for the capacitor C2. The switching element Q4 corresponds to a “fourth switch element” according to the present invention.

  The discharge circuit shown in FIG. 8B includes a series circuit of a resistor R2 and a capacitor C2, a switching element Q5, and a diode D2. The switching element Q5 is a transistor, the collector is connected to the gate of the snubber switch 11, and the emitter is connected to the source of the snubber switch 11. The diode D2 is connected between the collector and the emitter of the switching element Q5. The series circuit of the resistor R2 and the capacitor C2 is a time constant circuit, and is connected between the gate and source of the snubber switch 11. The connection point between the resistor R2 and the capacitor C2 is connected to the base of the switching element Q5. The switching element Q5 corresponds to a “fourth switching element” according to the present invention.

  The discharge circuit shown in FIG. 9A includes a series circuit of a resistor R2 and a capacitor C2, a switching element Q5, a diode D2, and a resistor R4. The resistor R4 is connected between the emitter of the switching element Q5 and the source of the snubber switch 11.

  The discharge circuit shown in FIG. 9B includes a resistor R5, a switching element Q5, and a diode D2. The resistor R5 is connected between the gate of the snubber switch 11 and the base of the switching element Q5.

  A switching element Q4 of the discharge circuit shown in FIG. 8A has a body diode, and a diode D2 is connected to the switching element Q5 shown in FIGS. 8B, 9A, and 9B. The body diode and the diode D2 function in the same manner as the diode D1 (see FIG. 6) described in the third embodiment, and can prevent a negative gate voltage from being applied to the snubber switch 11.

  Further, by providing the switching elements Q4 and Q5 and shortening the time for which the switching elements Q4 and Q5 are turned on by the time constant circuit, the time for extracting the gate charge of the snubber switch 11 can be shortened. That is, the snubber switch 11 can be turned off by lowering the gate voltage Vgs faster than in the third embodiment.

  FIG. 10 is a diagram showing waveforms of the voltage V2 across the auxiliary winding n23, the charging voltage V12 of the capacitor 12, and the gate voltage Vgs of the snubber switch 11. As described above, since the gate voltage Vgs can be reduced at a high speed, the snubber switch 11 is turned off at a higher speed than in the third embodiment.

(Embodiment 5)
FIG. 11 is a circuit diagram of the power converter 5 according to the fifth embodiment. This example is different from the first embodiment in that the snubber circuit 20 is also provided in the switching element Q32. In this example, a transformer T3 in which the choke coil L1 and the coils L2 and L3 are magnetically coupled is provided instead of the transformer T2.

  The snubber circuit 20 is a series circuit of a snubber switch 21 and a capacitor 22. The snubber switch 21 is a MOSFET and corresponds to a “third switch element” according to the present invention. A control circuit, which will be described later, is connected to the gate of the snubber switch 21 and is turned on and off by the control circuit. The snubber switch 21 is turned on when the switching element Q32 is turned off and turned off when the switching element Q32 is turned on.

  The control circuit is a series circuit in which the coil L3 and the auxiliary winding n24 are sequentially connected in series. In this series circuit, the coil L3 side is connected to one end side of the second winding n22 of the transformer T1, and the capacitor C3 side is connected to the gate of the snubber switch 21. The capacitor C3 is a capacitor for adjusting the voltage between the gate and the source of the snubber switch 21.

  Coil L3 is magnetically coupled to choke coil L1. The coil L3 corresponds to a “coil coupling winding” according to the present invention. The auxiliary winding n24 of the control circuit is magnetically coupled to the primary winding n11 of the transformer T1. The auxiliary winding n24 has a winding direction opposite to that of the auxiliary winding n23. The auxiliary winding n23 corresponds to a “transformer auxiliary winding” according to the present invention.

  In the present embodiment, the choke coil L1 has its winding start side (the side with the black circle of the choke coil L1 in the drawing) connected to the center tap (connection point P). The coil L2 is connected to the auxiliary winding n23 at the winding start side (the side with the black circle of the coil L2 in the drawing) and is connected to the source side of the snubber switch 11 at the winding end side. The coil L3 has its winding start side (the side with the black circle of the coil L3 in the drawing) connected to the auxiliary winding n24 and its winding end side connected to the source side of the snubber switch 21. When the winding start side of the choke coil L1 is connected to the output part OUT2, the winding end side of the coils L2, L3 is connected to the auxiliary windings n23, n24, and the winding start side of the coils L2, L3 is The snubber switches 11 and 21 may be connected to the source side.

  The control circuit for controlling the switching of the snubber switch 21 of the snubber circuit 20 is the same as the control circuit for the snubber circuit 10 described in the first embodiment, and a description thereof will be omitted.

  By providing the snubber circuit 20, a spike voltage generated when the switching element Q32 is turned off is absorbed by the capacitor 22, and damage to the switching element Q32 and its peripheral components can be prevented. Further, by adopting the above-described configuration such as providing the auxiliary winding n24, the power stress applied to the snubber switch 21 can be suppressed, and the snubber switch 21 can be prevented from being damaged.

  Thus, by providing the snubber circuits 10 and 20 in both the switching elements Q31 and Q32, the spike voltage generated when the switching elements Q31 and Q32 are turned off can be absorbed. Further, as described above, the switching elements Q31 and Q32 and their peripheral circuits can be appropriately protected.

  Note that the snubber circuit and the corresponding control circuit may be provided only for the switching element Q32. Moreover, you may make it combine the structure of Embodiment 2-4 with the power converter device 5 of Embodiment 5. FIG. In addition, the configurations of the respective embodiments may be arbitrarily combined as appropriate.

C1, C2, C3 ... Capacitor Co ... Smoothing capacitors D1, D2 ... Diodes IN1, IN2 ... Input section L1 ... Choke coil L2, L3 ... Coil n11 ... Primary winding n21 ... First winding n22 ... Second winding n23 , N24 ... auxiliary windings OUT1, OUT2 ... output part P ... connection point (center tap)
Q11, Q12, Q21, Q22 ... switching elements Q31, Q32 ... switching elements Q4, Q5 ... switching elements R1, R2, R4, R5 ... resistors T1, T2, T3 ... transformers 1, 2, 3, 5 ... power converter 10 , 20 ... Snubber circuits 11, 21 ... Snubber switches 12, 22 ... Capacitors

Claims (4)

A transformer having a primary winding to which an alternating voltage is applied, and a secondary winding having a first end, a second end, and a center tap;
A first switch element connected between the first end and the first output unit;
A second switch element connected between the second end and the first output unit;
A choke coil connected between the center tap and the second output unit;
A snubber circuit having a third switch element and a first capacitor connected in series, and connected in parallel to at least one of the first switch element or the second switch element;
A control circuit for turning on and off the third switch element;
With
The control circuit has a series circuit of a transformer auxiliary winding magnetically coupled to the primary winding of the transformer and a coil coupling winding magnetically coupled to the choke coil,
The series circuit is connected between a control terminal of the third switch element and the first end of the secondary winding;
Of the primary winding and the secondary winding, one of a winding portion between the center tap and the first end, or one of a winding portion between the center tap and the second end, , The turns ratio of the auxiliary transformer winding is represented by N1: N2: N3, and the turns ratio of the choke coil and the coil coupling winding is represented by N4: N5, m = N5 / N4, n = N2 / N1, and n1 = N3 / N1,
mn−n1 = 0 is satisfied,
Power conversion device. The series circuit further includes a second capacitor;
A resistance element connected between the control terminal of the third switch element and the first end of the secondary winding;
A differentiation circuit is formed by the second capacitor and the resistance element.
The power conversion device according to claim 1. A diode having a cathode connected to the control terminal of the third switch element and an anode connected to a reference potential terminal of the third switch element;
The power converter according to claim 1 or 2 provided with. A fourth switch element connected between a control terminal of the third switch element and a reference potential terminal;
A time constant circuit for turning on the fourth switch element with a set time constant when the third switch element is turned on;
With
When the fourth switch element is turned on, the third switch element is turned off.
The power converter device in any one of Claim 1 to 3.

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