JP6361610B2 - Switching element driving device - Google Patents

Description

  The present invention relates to a switching element driving device for driving a switching element.

  When driving a switching element, it is effective to perform switching at high speed in order to reduce switching loss. However, when switching speed is increased, problems such as EMI (electromagnetic interference) noise and surge occur. Specifically, ringing occurs in the output current of the switching element.

  In order to cope with this problem, for example, in Patent Document 1, a current source circuit for supplying a current for discharging the gate capacitance when the switching element is turned off, and a current value for discharging the gate capacitance by the current source circuit, There has been proposed a gate drive circuit provided with a current adjustment circuit that gradually decreases as the voltage across the main terminal of the switching element increases.

  In Patent Document 2, the gate charge discharge path immediately after the switching element is turned off is divided into two systems. When the drain voltage decreases due to the rapid discharge of the gate charge by the two system discharge paths, one discharge path is closed, There has been proposed a drive circuit that slowly discharges only through the other one discharge path.

JP 2008-67593 A JP 2001-45740 A

  In both of the drive circuits proposed in Patent Document 1 and Patent Document 2, the switching speed is increased by discharging the gate capacitance with a relatively large current value in the initial stage of switching immediately after the switching element is turned off. Further, in the latter half of switching in which the discharge of the gate capacitance has advanced, the switching speed is reduced by reducing the current value, thereby suppressing the occurrence of surge. Therefore, these drive circuits can achieve both reduction of switching loss and suppression of occurrence of surge.

  However, the gate drive circuit in Patent Document 1 requires a current source circuit and a current adjustment circuit in order to adjust the current value for discharging the gate capacitance, leading to an increase in circuit size and cost. There is. Also, in the drive circuit of Patent Document 2, two MOSFETs and a monostable multivibrator circuit are provided to open and close one discharge path, and the circuit size is increased in the same manner as the gate drive circuit of Patent Document 1. There is a problem of incurring cost increase.

  The present invention has been made in view of the above-described points, and an object of the present invention is to provide a switching element driving device having a simpler configuration while being able to achieve both high speed switching and suppression of ringing of output current. To do.

In order to achieve the above object, a switching element driving apparatus according to the present invention comprises:
A switching element having a control terminal, a first terminal, and a second terminal, wherein the first terminal and the second terminal are in a conductive state or a non-conductive state according to a voltage applied to the control terminal ( 50),
The voltage applied to the control terminal of the switching element is controlled, and when the switching element is changed from the conductive state to the non-conductive state, the control terminal is set to the second terminal in order to reduce the potential difference between the control terminal and the second terminal. A driver circuit (20) connected to a connection destination having the same potential as the terminal;
A driver circuit comprising a parallel circuit (30) of a capacitor (31) and an impedance element (32) inserted in a path connecting a control terminal to a connection destination having the same potential as the second terminal ;
The switching element has a control terminal capacitance in which electric charges are accumulated in the control terminal in the conductive state,
The capacitance C ₁ of the capacitor, the control terminal capacitance C _gs of the switching _element, the control terminal capacitance is charged, the control terminal voltage V _gg, the switching element becomes conductive when the switching element is in a conductive state The on-threshold voltage _Vth satisfies the relationship of the following formula 2 .

  The driver circuit (20) connects the control terminal of the switching element to a connection destination having the same potential as the second terminal when the switching element (50) is changed from the conductive state to the non-conductive state, that is, when the switching element is turned off. To do. Immediately after this connection, since the capacitor (31) is not charged, a voltage having substantially the same potential as that of the second terminal is applied to the control terminal, and the switching element starts switching for turning off at high speed. However, when the potential difference between the control terminal and the second terminal increases with the charging of the capacitor (31), the switching speed is slowed accordingly. As a result, with the simple configuration as described above, the switching speed is increased at the initial stage of switching to reduce the switching loss, and the switching speed is reduced as the switching progresses, thereby suppressing the occurrence of ringing. Is possible. The electric charge charged in the capacitor is discharged through the impedance element (32) with the passage of time.

  In addition to the above-described configuration, the configuration described below may be adopted in order to achieve both high-speed switching and suppression of output current ringing when the switching element is turned on. That is, the main power source (10) connected to the driver circuit, and the input capacitor (13) connected in parallel to the driver circuit with respect to the main power source and arranged without any element other than wiring between the driver circuit and the main power source (10). And an input impedance element (12) connected in series with the input capacitor and the driver circuit with respect to the main power supply, and disposed without any elements other than wiring between the input capacitor and the driver circuit. The driver circuit may be configured to connect the main power source to the control terminal via the input impedance element when the switching element is changed from the non-conductive state to the conductive state.

  When the switching element (50) is in the off state, the input capacitor (13) is charged by the main power supply (10). For this reason, immediately after the driver circuit (20) starts the operation for turning on the switching element, that is, immediately after connecting the main power supply to the control terminal, the control terminal of the switching element is almost equivalent to the main power supply by the input capacitor. Is applied. For this reason, the switching element can immediately start switching for turning on, and the switching speed can be increased.

  Here, the charge accumulated in the input capacitor is reduced by being injected into the control terminal of the switching element. When the charge stored in the input capacitor decreases, it is compensated by the main power supply. However, an input impedance element (12) having a predetermined impedance is arranged between the input capacitor and the main power source. For this reason, a delay occurs in the movement of charges from the main power supply to the input capacitor. As a result, the intermediate potential between the driver circuit and the input impedance element starts to decrease at the same time when the driver circuit starts an operation for turning on the switching element. In other words, the voltage applied to the control terminal of the switching element starts to decrease. As described above, the input capacitor and the input impedance element act to reduce the drive capability of the driver circuit at the same time that the driver circuit starts an operation for turning on the switching element. Therefore, ringing of the output current can be suppressed.

  The reference numerals in the parentheses merely show an example of a correspondence relationship with a specific configuration in an embodiment described later in order to facilitate understanding of the present invention, and are intended to limit the scope of the present invention. Not intended.

  Further, the technical features described in the claims of the claims other than the features described above will become apparent from the description of embodiments and the accompanying drawings described later.

It is a circuit diagram which shows the structure of the switching element drive device which concerns on 1st Embodiment. It is a wave form diagram which shows the mode of the change of drain voltage and drain current at the time of turning off a switching element. It is a circuit diagram which shows the structure of the switching element drive device which concerns on 2nd Embodiment. It is a wave form diagram which shows the mode of the change of a drain current and a drive voltage when turning on a switching element. It is a circuit diagram which shows the structure of the modification of 1st Embodiment. It is a circuit diagram which shows the structure of the modification of 1st Embodiment. It is a circuit diagram which shows the structure of the modification of 1st Embodiment. It is a circuit diagram which shows the structure of the modification of 1st Embodiment.

  Embodiments of the present invention will be described below with reference to the drawings.

(First embodiment)
FIG. 1 is a diagram illustrating a configuration of the switching element driving apparatus according to the first embodiment. Note that the switching element to be driven by the switching element driving apparatus according to the present embodiment has a control terminal, a first terminal, and a second terminal, and the first terminal and the switching terminal according to the voltage applied to the control terminal. The switching element is in a conductive state or a non-conductive state between the second terminal. Specifically, as a switching element, a power semiconductor element such as MOSFET or IGBT using silicon (Si) or silicon carbide (SiC) as a semiconductor material, compound semiconductor material (eg, GaN, GaAs, etc.) or diamond is used. It may be a conventional transistor (for example, MESFET, heterojunction FET, HEMT, etc.).

  Such a switching element has a control terminal capacity (for example, gate capacity) in which electric charges are accumulated in a control terminal (for example, the gate of a MOSFET). When the control terminal capacitance is charged and the voltage applied to the control terminal becomes equal to or higher than the ON threshold voltage, the first terminal and the second terminal (for example, the drain and source of the MOSFET) of the switching element are brought into conduction. . Conversely, when the control terminal capacitance is discharged and the voltage applied to the control terminal falls below the ON threshold voltage, the first terminal and the second terminal of the switching element become non-conductive. In the following embodiments, an example in which a MOSFET is employed as a switching element will be described.

  As shown in FIG. 1, a load 60 is connected in series to a MOSFET 50 serving as a switching element. The switching element driving apparatus according to the present embodiment controls the amount of current flowing through the MOSFET 50, that is, the amount of current flowing through the load 60 by, for example, PWM controlling the MOSFET 50.

  As shown in FIG. 1, the switching element driving apparatus according to the present embodiment includes a main power supply 10, a driver circuit 20, a parallel circuit 30, and a control circuit 40 as main components.

  The main power supply 10 supplies a voltage to the driver circuit 20. The driver circuit 20 applies a voltage to the gate of the MOSFET 50 using the voltage supplied from the main power supply 10 to turn on the MOSFET 50. A capacitor 11 is connected to the main power supply 10 in parallel. The capacitor 11 is for stabilizing the voltage supplied from the main power supply 10 to the driver circuit 20.

  The driver circuit 20 includes an on-side switch 21 and an off-side switch 22, and the on-side switch 21 and the off-side switch 22 are connected in series. One end of the on-side switch 21 is connected to the main power supply 10, and a connection line connecting the other end of the on-side switch 21 and one end of the off-side switch 22, that is, the middle point of both the switches 21, 22 is the MOSFET 50. The other end of the off-side switch 22 is connected to the parallel circuit 30. Note that both the on-side switch 21 and the off-side switch 22 in the present embodiment are composed of MOS transistors.

  When the MOSFET 50 is turned on, the driver circuit 20 turns on the on-side switch 21 and turns off the off-side switch 22. As a result, the voltage supplied from the main power supply 10 is applied to the gate of the MOSFET 50 via the on-side switch 21 and the MOSFET 50 is turned on. On the other hand, when the MOSFET 50 is turned off, the driver circuit 20 turns off the on-side switch 21 and turns on the off-side switch 22. As a result, the gate of the MOSFET 50 is connected to the source via the off-side switch 22 and the parallel circuit 30 described later. As a result, the potential difference between the gate and the source of the MOSFET 50 is reduced, so that the MOSFET 50 is turned off.

  The parallel circuit 30 includes a capacitor 31 and a resistor 32 as an impedance element. As described above, one end of the parallel circuit 30 is connected to the other end of the off-side switch 22, and the other end of the parallel circuit 30 is connected to the source of the MOSFET 50. For this reason, when the off-side switch 22 is turned on, the gate of the MOSFET 50 is connected to the source via the off-side switch 22 and the parallel circuit 30. When the off-side switch 22 is turned on, the capacitor 31 of the parallel circuit 30 is charged by a current discharged from the gate capacitance of the MOSFET 50, and adjusts the gate-source potential difference of the MOSFET 50. The resistor 32 is provided to discharge the charge charged in the gate capacitance of the MOSFET 50 and the capacitor 31 over time.

  For example, the control circuit 40 outputs a control signal to the on-side switch 21 and the off-side switch 22 of the driver circuit 20 so that the MOSFET 50 is turned on and off according to a target duty ratio given from the outside.

  Next, with reference to FIG. 1 and FIG. 2, the effect of the switching element drive device which concerns on this embodiment is demonstrated. FIG. 2 is a waveform diagram showing changes in the drain voltage and drain current when the MOSFET 50 shifts from the on state to the off state, that is, when the MOSFET 50 is turned off.

  When the MOSFET 50 is on, the on-side switch 21 of the driver circuit 20 is on and the off-side switch 22 is off. From this state, when the MOSFET 50 is to be turned off, the on-side switch 21 is switched off and the off-side switch 22 is switched on. As a result, the power supply from the main power supply 10 is cut off, and the gate of the MOSFET 50 is connected to the source of the MOSFET 50 via the off-side switch 22 and the parallel circuit 30. In FIG. 2, the timing when the on-side switch 21 and the off-side switch 22 are switched between the on and off states is shown as time t.

  While the MOSFET 50 is turned on, that is, while the off-side switch 22 is turned off, the charge of the capacitor 31 is discharged through the resistor 32, and the capacitor 31 is in an uncharged state. Therefore, when the off-side switch 22 is turned on, a voltage having almost the same potential as the source potential is instantaneously applied to the gate of the MOSFET 50 through the capacitor 31, and the MOSFET 50 starts switching for turning off at high speed. .

  However, while the MOSFET 50 is on, the gate capacitance of the MOSFET 50 is charged. For this reason, when the on-side switch 21 is switched off and the off-side switch 22 is switched on, the discharge of charges from the gate capacitance is started. The capacitor 31 is charged by this discharge charge. As the charging of the capacitor 31 proceeds, the potential difference between the gate and the source of the MOSFET 50 increases. For this reason, the switching speed of turn-off of the MOSFET 50 can be slowed according to an increase in the potential difference between the gate and the source. Thereby, the fluctuation (ringing) of the drain voltage and drain current when the MOSFET 50 shifts to the off state can be reduced.

  In FIG. 2, the state of changes in drain voltage and drain current when the MOSFET 50 is turned off by the switching element driving circuit of the present embodiment is shown by a solid line. Further, as a first comparative example, a change of drain voltage and drain current when the parallel circuit 30 is removed from the configuration of the switching element driving circuit of the present embodiment is shown by a chain line. Further, as a second comparative example, drain voltage and drain when the parallel circuit 30 is removed from the configuration of the switching element driving circuit of the present embodiment and a resistor is provided between the driver circuit 20 and the gate of the MOSFET 50. A state of change in current is indicated by a two-dot chain line.

  In the first comparative example, since the gate of the MOSFET 50 is directly connected to the source immediately after the off-side switch 22 is turned on, switching for turn-off is started immediately. That is, as indicated by the alternate long and short dash line in FIG. 2, the drain voltage increases and the drain current decreases within a very short time. However, in the first comparative example, since the parallel circuit 30 is not provided, the drain voltage rises and the drain current decreases rapidly, and as a result, the drain voltage and drain current when the MOSFET 50 shifts to the off state. Fluctuations (ringing) will also increase.

  In order to prevent this ringing, when a resistor is inserted between the driver circuit 20 and the gate of the MOSFET 50 as in the second comparative example, the discharge from the gate capacitance can be performed slowly. As a result, as indicated by a two-dot chain line in FIG. 2, ringing of the drain voltage and drain current when the MOSFET 50 is turned off can be suppressed.

  However, in the second comparative example, since the discharge from the gate capacitance is suppressed immediately after the off-side switch 22 is turned on, the time until the drain voltage and the drain current start to change becomes long. That is, the switching speed for turning off the MOSFET is reduced.

  In contrast to the first and second comparative examples, according to the switching element driving apparatus of the present embodiment, as described above, the switching speed at the initial stage of switching for turn-off immediately after the off-side switch 22 is turned on. Can be increased. That is, as shown in FIG. 2, according to the switching element driving apparatus of the present embodiment, the drain voltage and the drain current start to change at substantially the same time as the first comparative example. Equivalent switching speed is obtained.

  Furthermore, in the switching element driving apparatus of this embodiment, the capacitor 31 is charged by the discharge from the gate capacitance of the MOSFET 50, and as a result, the potential difference between the gate and the source increases. This increase in potential difference acts in the direction of decreasing the switching speed of the MOSFET 50. For this reason, as shown in FIG. 2, changes in the drain voltage and the drain current are gentler than those in the first comparative example. As a result, the magnitude of the ringing of the drain voltage and drain current when the MOSFET 50 shifts to the off state can be reduced to the same magnitude as that of the second comparative example.

  Thus, according to the switching element driving apparatus according to the present embodiment, it is possible to achieve both reduction of switching loss and suppression of occurrence of ringing with a very simple configuration. The electric charge charged in the capacitor 31 is discharged through the resistor 32 as time passes.

Here, a preferable range regarding the capacitance C ₁ of the capacitor 31 of the parallel circuit 30 and a preferable range regarding the resistance value R ₁ of the resistor 32 will be described.

As described above, the capacitor 31 of the parallel circuit 30 is charged by discharging from the gate capacitance C _{gs of the} MOSFET 50, and the potential difference between the gate and the source is adjusted by the charging. When the gate potential exceeds the ON threshold voltage _Vth of the MOSFET 50 due to the charging of the capacitor 31, the turn-off operation of the MOSFET 50 does not proceed smoothly. Therefore, the capacitance C ₁ of the capacitor 31, it is preferable to satisfy the relationship shown in Equation 1 below. Note that the gate voltage when the MOSFET 50 is on is V _gg .

By transforming Equation 1, the range of the capacity C ₁ shown in Equation 2 below can be obtained.

Next, a description will be given resistance value _{R 1} of the resistor 32. The charges charged in the gate capacitance C _{gs of the} MOSFET 50 and the capacitor 31 are discharged through the resistor 32. This discharge then needs to be substantially completed by the time the MOSFET 50 is turned on. Therefore, the driver circuit 20 turns off the MOSFET 50 during the period from when the on-side switch 21 is turned off and the off-side switch 22 is turned on until the on-side switch 21 is turned on and the off-side switch 22 is turned off. When the off time T _off is set, the resistance value R ₁ of the resistor 32 preferably satisfies at least the condition of Equation 3 below.

However, there is a possibility that the discharge from the gate capacitance C _gs of the MOSFET 50 and the capacitor 31 may not be completely completed with the off time T _off only by satisfying the condition of Equation 3. Therefore, it is preferable that the time constants of the gate capacitance C _gs and the capacitance C _{1 of the} capacitor 31 and the resistance value R ₁ of the resistor 32 are shorter than ¼ of the off time T _off . Furthermore, shorter than 1/10 of the off time _{T off,} can be more reliably within the off time _{T off,} to complete the discharge from the capacitive _{C 1} gate capacitance _{C gs} and a capacitor 31.

(Second Embodiment)
Next, with reference to FIG.3 and FIG.4, the switching element drive device which concerns on 2nd Embodiment is demonstrated.

  The switching element driving device according to the first embodiment described above is intended to increase the switching speed and reduce ringing when the switching element is turned off. On the other hand, the switching element driving apparatus according to the second embodiment can further increase the switching speed and reduce ringing when the switching element is turned on.

  Therefore, as shown in FIG. 3, the switching element driving device according to the present embodiment includes an input impedance element 12 and an input capacitor 13 in addition to the configuration of the first embodiment. Other configurations are the same as those of the switching element driving apparatus of the first embodiment.

  The input capacitor 13 is connected to the main power supply 10 in parallel with the driver circuit 20. The input capacitor 13 is connected to the driver circuit 20 without passing through any element except for the wiring.

  The input impedance element 12 is, for example, a resistor, and is connected between the main power supply 10 and the input capacitor 13 and in series with the input capacitor 13 with respect to the main power supply 10. In other words, the input capacitor 13 and the driver circuit 20 are in parallel with the impedance element 12. The impedance element 12 is connected to the positive electrode side of the main power supply 10. The capacitor 11 is in parallel connection with the impedance element 12 with respect to the main power supply 10, and no element other than wiring is interposed between the capacitor 11 and the impedance element 12.

In the present embodiment, the potential on the high potential side in a state where the input capacitor 13 is sufficiently charged is represented as V _dr . V _dr is a potential obtained by subtracting the voltage drop caused by the impedance element 12 from the voltage across the main power supply 10.

  Next, with reference to FIG. 3 and FIG. 4, the effect of the switching element drive device which concerns on this embodiment is demonstrated. FIG. 4 is a waveform diagram showing changes in the drive voltage and drain current supplied by the driver circuit 20 when the MOSFET 50 shifts from the off state to the on state, that is, when the MOSFET 50 is turned on. is there.

  In the state where the MOSFET 50 is turned off, the on-side switch 21 of the driver circuit 20 is turned off and the off-side switch 22 is turned on. From this state, when the MOSFET 50 is to be turned on, the on-side switch 21 is switched on and the off-side switch 22 is switched off. As a result, power supply from the main power supply 10 side to the gate of the MOSFET 50 is started. In FIG. 4, the timing when the on-side switch 21 and the off-side switch 22 are switched between the on and off states is shown as time t1.

When the MOSFET 50 is off, the input capacitor 13 is charged by the main power supply 10. For this reason, when the on-side switch 21 is turned on so that the driver circuit 20 turns on the MOSFET 50, the high-potential-side voltage V _dr of the input capacitor 13 that is substantially equivalent to the main power supply 10 is applied to the gate of the MOSFET 50. For this reason, the MOSFET 50 can quickly start switching for turn-on, and the switching speed can be increased.

Here, the charge accumulated in the input capacitor 13 is reduced by being injected into the gate of the MOSFET 50. When the stored charge in the input capacitor 13 decreases, it is compensated by the main power supply 10 or the capacitor 11. However, an input impedance element 12 having a predetermined impedance is disposed between the input capacitor 13 and the main power supply 10 or the capacitor 11. For this reason, a delay occurs in the movement of charges from the main power supply 10 or the capacitor 11 to the input capacitor 13, and the discharge speed of the input capacitor 13 exceeds the compensation speed. As a result, the high potential side voltage V _dr of the input capacitor 13, which is an intermediate potential between the driver circuit 20 and the input impedance element 12, is the time when the driver circuit 20 starts the turn-on operation of the MOSFET 50 as shown in FIG. It starts to decrease from (time t1). In other words, the drive voltage supplied from the driver circuit 20 and applied to the gate of the MOSFET 50 starts to decrease. At time t2, when the discharge rate of the input capacitor 13 becomes lower than the compensation rate, charges start to be accumulated in the input capacitor 13, and thereafter, the drive voltage increases.

  As described above, the input capacitor 13 and the input impedance element 12 act so that the driver circuit 20 starts an operation for turning on the MOSFET 50 and at the same time reduces the drive capability of the driver circuit 20. Therefore, ringing of the output current of MOSFET 50 can be effectively suppressed.

  In FIG. 4, changes in drive voltage and drain current when the MOSFET 50 is turned on by the switching element drive circuit of the present embodiment are shown by solid lines. Further, as a comparative example, a change of the drive voltage and the drain current when the input impedance element 12 and the input capacitor 13 are removed from the configuration of the switching element drive circuit of the present embodiment is indicated by a chain line.

  In the configuration in which the input impedance element 12 and the input capacitor 13 are not provided as in the comparative example, the drive voltage is a constant voltage defined by the main power supply 10 as shown by a one-dot chain line in FIG. In such a configuration, since the voltage defined by the main power supply 10 is always applied to the gate of the MOSFET 50, the drain current increases steeply and large ringing occurs.

  On the other hand, according to the configuration of the present embodiment, the drive voltage of the driver circuit 20 can be temporarily reduced because the drive voltage can be lowered immediately after the time t1 by the action of the input impedance element 12 and the input capacitor 13. Di / dt can be suppressed. Therefore, as shown by the solid line in FIG. 2, ringing of the drain current can be suppressed.

  In addition, since the maximum value of the drive voltage can be applied to the gate of the MOSFET 50 at time t1, the rise of the drain current, that is, di / dt can be made substantially equal to the conventional configuration. In other words, high-speed switching can be realized.

Next, it will be described quantitatively capacitance C ₂ of the input capacitor 13. When the gate capacitance of the MOSFET 50 is C _gs and the drive voltage after the time t1 is V (t), the total amount of charge does not change before and after the time t1, so the following formula 4 is established.

Since V (t) must always be larger than the ON threshold voltage _Vth of the MOSFET 50, when Formula 4 is solved for V (t) and the condition V (t)> _Vth is applied, Formula 5 is It holds.

On the other hand, V (t) is expected to reduce the driving capacity when lowered even slightly relative to _{V dr,} for example, to make V (t) is less than 90% of Vdr is Equation 4 V ( It is sufficient to solve for t) and apply V (t) <0.9 Vdr, and Equation 6 holds.

From the above, the capacitance C ₂ of the input capacitor 13 is equal to the gate capacitance C _{gs of the} MOSFET 50 and the intermediate potential V _dr between the driver circuit 20 and the impedance element 12 when the input capacitor 13 is sufficiently charged. If the relationship of Expression 7 is satisfied, the above-described effects can be obtained.

Here, even if the drive voltage V (t)> _Vth is satisfied, if V (t) takes a value in the vicinity of _Vth , the rise of the drain current, that is, di / dt becomes too small, resulting in a switching loss. It can get worse. Further, if the rate of decrease of V (t) with respect to V _{dr is} about 50%, which is smaller than 90%, a further ringing suppression effect can be expected. Therefore, the capacitance C ₂ is more preferably satisfies the formula 8.

Here, V ₀ is a constant that satisfies 1 <V ₀ <20. If the capacitance C ₂ satisfies C ₂ <3C _gs , a further ringing suppression effect can be expected.

Next, the impedance of the input impedance element 12 will be described quantitatively. In the present embodiment, the case is the input impedance element 12 is a resistor the resistance value R _2. In the following description, the unit of capacitance is F, the unit of resistance is Ω, and the unit of frequency is Hz.

First, consider the lower limit of the resistance value R _2. In order to exert the above-described effects, it is necessary to suppress the drive capability of the driver circuit 20 in the transition period of the rise of the drain current. Decrease in driving capability can be realized by not reached on the amount of charge the charge of the input capacitor 13 is defined in the capacitor C _2. In other words, the charging time of the input capacitor 13 must be longer than the switching time, which is the time from the start of drain current rise to completion.

The charging time of the input capacitor 13 is about e times the charging time constant (= C ₂ R ₂ ). Here, e is the number of Napiers. Therefore, assuming that the minimum value of the switching time is 10 ns, eC ₂ R ₂ > 10 × 10 ⁻⁹ .

Then, consider the upper limit of the resistance value R _2. The MOSFET 50 is periodically turned on / off at a predetermined frequency, which is synchronized with the on / off of the on-side switch 21 in the driver circuit 20. The drive voltage, that is, the high potential side voltage _Vdr of the input capacitor 13 must be restored to its maximum value after the on-side switch 21 is turned off and then on again.

The time from when the on-side switch 21 is turned off to when it is turned on again can be expressed as (1-D) / f using the carrier frequency f that is the driving frequency of the MOSFET 50 and the duty ratio D. The relationship with the charging time of 13 (= eC ₂ R ₂ ) is as shown in Equation 10.

As described above, the resistance value R ₂ [Ω] of the input impedance element 12 satisfies the relationship of Expression 11 with respect to the capacitance C ₂ [F], the carrier frequency f [Hz], and the duty ratio D of the input capacitor 13. It is preferable to set to.

  However, in the above example, the minimum value of the switching time is assumed to be 10 ns. However, there may be a case where sufficient charging time cannot be secured for the MOSFET 50 whose switching time is longer than 10 ns.

Further, the upper limit of the resistance value R _2, the resistance value R ₂ have shown that it is preferable to satisfy the formula 10, which, after the on-side switch 21 is turned off, the time to turn on again (1 This indicates that the charging time (= eC ₂ R ₂ ) of the input capacitor 13 is small with respect to -D) / f. However, under the condition of (1-D) / f≈eC ₂ R ₂ , the high potential side voltage V _dr of the input capacitor 13 after charging may not be stable.

Therefore, for example, it is also effective for the MOSFET 50 having a switching time longer than 10 μs, and it is preferable to satisfy Expression 12 in order to sufficiently stabilize the high potential side voltage V _dr of the input capacitor 13.

  The input impedance element 12 may employ, for example, a coil having a self-inductance L in addition to a resistor. Below, the example which employ | adopted the coil as the input impedance element 12 is demonstrated. In the following description, the unit of capacitance is F, the unit of self-inductance is H, and the unit of frequency is Hz. Further, e is the number of Napiers, and π is the circumference ratio.

First, the lower limit of the self-inductance L is examined. In this case, the charging time constant C ₂ R ₂ of the input capacitor 13 may be replaced with 2π (C ₂ L) ^1/2 with respect to the second embodiment described above. That is, the self-inductance L preferably satisfies Equation 13.

Next, the upper limit of the self-inductance L is examined. As for the upper limit, the charging time constant C ₂ R ₂ of the input capacitor 13 may be replaced with 2π (C ₂ L) ^1/2 as compared with the second embodiment described above. That is, the self-inductance L preferably satisfies Equation 14.

From the above, the self-inductance L [H] of the impedance element 12 is set so as to satisfy the relationship of Expression 15 with respect to the capacitance C ₂ [F] of the input capacitor 13, the carrier frequency f [Hz], and the duty ratio D. It is preferable to do.

  The preferred embodiments of the present invention have been described above. However, the present invention is not limited to the above-described embodiments, and various modifications can be made without departing from the spirit of the present invention.

  For example, in the first embodiment described above, when the MOSFET 50 is turned off, the driver circuit 20 connects the gate of the MOSFET 50 to the source of the MOSFET 50 via the parallel circuit 30. However, it is sufficient that the connection destination has almost the same potential as the source, and the connection destination does not need to be the source itself.

  For example, as shown in FIG. 5, when a shunt resistor 70 for detecting a load current is connected to the source of the MOSFET 50, the driver circuit 20 turns the MOSFET 50 gate through the parallel circuit 30 when turning off the MOSFET 50. Alternatively, it may be connected to the downstream side of the shunt resistor 70. Further, as shown in FIG. 6, when a coil 71 that generates a magnetic flux having a magnitude corresponding to the load current is used for load current detection, the coil 71 may be connected to the downstream side of the coil 71. .

In the first embodiment described above, by setting the capacitance C ₁ of the capacitor 31 within the range shown in Formula 2, even if the capacitor 31 is charged by the discharge from the gate capacitance C _gs of the MOSFET 50, the gate potential is The ON threshold voltage _Vth of the MOSFET 50 is not exceeded.

However, regardless of the setting of the capacitance C ₁ of the capacitor 31, for example, as shown in FIG. 7, to be connected in parallel to the Zener diode 80 having a lower zener voltage than the ON threshold voltage of the MOSFET50 against capacitor 31 May be. Even with this configuration, even if the potential of the capacitor 31 rises due to the discharge from the gate capacitance C _{gs of} the MOSFET 50, it is possible to prevent the ON threshold voltage V _th of the MOSFET 50 from being exceeded.

  Alternatively, instead of the Zener diode 80, as shown in FIG. 8, another MOSFET 81 having an ON threshold voltage lower than that of the MOSFET 50 is connected in parallel to the capacitor 31, and the voltage on the high potential side of the capacitor 31 is used as the gate. You may connect. Also in this case, even if the potential rises due to charging of the capacitor 31, the upper limit of the potential can be suppressed to be equal to or lower than the ON threshold voltage of the MOSFET 81.

  In this case, the capacitor 31 may be omitted when the MOSFET 81 has a gate capacitance that is large enough to perform the function that the capacitor 31 should perform.

  Further, in the above-described second embodiment, the configuration having the capacitor 11 has been described, but the above-described effects can be achieved even with a configuration in which the capacitor 11 is not disposed. However, since the capacitor 11 stabilizes the voltage of the main power supply 10, it is preferable to have the capacitor 11.

  In the first and second embodiments described above, an example in which the driver circuit 20 is configured by two MOS transistors has been described. However, the driver circuit 20 may be configured by another switch.

DESCRIPTION OF SYMBOLS 10 ... Main power supply 12 ... Input impedance element 13 ... Input capacitor 20 ... Driver circuit 30 ... Parallel circuit 40 ... Control circuit 50 ... Switching element 60 ... Load

Claims (12)

Switching having a control terminal, a first terminal, and a second terminal, wherein the first terminal and the second terminal are turned on or off according to the voltage applied to the control terminal. An element (50);
In order to reduce the potential difference between the control terminal and the second terminal when controlling the voltage applied to the control terminal of the switching element, and when switching the switching element from a conductive state to a non-conductive state, A driver circuit (20) for connecting the control terminal to a connection destination having the same potential as the second terminal;
A parallel circuit (30) of a capacitor (31) and an impedance element (32) inserted in a path connecting the control terminal to a connection destination having the same potential as the second terminal ;
The switching element has a control terminal capacitance in which electric charges are accumulated in the control terminal in a conductive state,
The capacitance C ₁ of the capacitor includes a control terminal capacitance C _{gs of} the switching element, a control terminal voltage V _gg when the control terminal capacity is charged and the switching element is in a conductive state, and the switching element. A switching element driving device characterized by satisfying the relationship of the following formula 1 with respect to the ON threshold voltage _{Vth at} which becomes conductive .

The impedance element is a resistor, and the resistance value R ₁ of the resistor includes a capacitance C _{1 of} the capacitor, a control terminal capacitance C _{gs of} the switching element, and a time T _off when the switching element is turned _off. On the other hand, the switching element driving apparatus according to claim 1, wherein the relationship of the following formula 2 is satisfied .

Switching having a control terminal, a first terminal, and a second terminal, wherein the first terminal and the second terminal are turned on or off according to the voltage applied to the control terminal. An element (50);
In order to reduce the potential difference between the control terminal and the second terminal when controlling the voltage applied to the control terminal of the switching element, and when switching the switching element from a conductive state to a non-conductive state, A driver circuit (20) for connecting the control terminal to a connection destination having the same potential as the second terminal;
A parallel circuit (30) of a capacitor (31) and an impedance element (32) inserted in a path connecting the control terminal to a connection destination having the same potential as the second terminal;
The impedance element is a resistor, and the resistance value R ₁ of the resistor includes a capacitance C _{1 of} the capacitor, a control terminal capacitance C _{gs of} the switching element, and a time t _off when the switching element is turned _off. On the other hand, a switching element driving device satisfying the relationship of the following formula 2 .

Switching having a control terminal, a first terminal, and a second terminal, wherein the first terminal and the second terminal are turned on or off according to the voltage applied to the control terminal. An element (50);
In order to reduce the potential difference between the control terminal and the second terminal when controlling the voltage applied to the control terminal of the switching element, and when switching the switching element from a conductive state to a non-conductive state, A driver circuit (20) for connecting the control terminal to a connection destination having the same potential as the second terminal;
A parallel circuit (30) of a capacitor (31) and an impedance element (32) inserted in a path connecting the control terminal to a connection destination having the same potential as the second terminal;
A voltage rise prevention element (80, 81) connected in parallel with the capacitor and preventing a voltage applied to the control terminal of the switching element by charging the capacitor from being equal to or higher than an ON threshold voltage of the switching element. switching element driving apparatus, characterized in that it comprises a. The voltage rise prevention element includes a Zener diode (80) having a breakdown voltage lower than the ON threshold voltage of the switching element, and another switching element (81) having an ON voltage threshold lower than the ON threshold voltage of the switching element. The switching element driving device according to claim 4 , wherein the switching element driving device is any one of the following. A main power supply (10) connected to the driver circuit;
An input capacitor (13) connected in parallel to the driver circuit with respect to the main power supply and disposed without any element other than wiring between the driver circuit,
An input impedance element (12) connected in series with the input capacitor and the driver circuit with respect to the main power supply, and disposed without an element other than wiring between the input capacitor and the driver circuit; With
Said driver circuit, when in a conductive state the switching element from the non-conducting state, through the input impedance element, either said main power supply of claims 1 to 5, characterized in that connected to the control terminal The switching element driving device according to claim 1. It said driver circuit via the parallel circuit, switching element driving device according to any one of claims 1 to 6, characterized in that connecting the control terminal to the second terminal. Switching having a control terminal, a first terminal, and a second terminal, wherein the first terminal and the second terminal are turned on or off according to the voltage applied to the control terminal. An element (50);
In order to reduce the potential difference between the control terminal and the second terminal when controlling the voltage applied to the control terminal of the switching element, and when switching the switching element from a conductive state to a non-conductive state, A driver circuit (20) for connecting the control terminal to a connection destination having the same potential as the second terminal;
A parallel circuit (30) of a capacitor (31) and an impedance element (32) inserted in a path connecting the control terminal to a connection destination having the same potential as the second terminal;
A main power supply (10) connected to the driver circuit;
An input capacitor (13) connected in parallel to the driver circuit with respect to the main power supply and disposed without any element other than wiring between the driver circuit,
An input impedance element (12) connected in series with the input capacitor and the driver circuit with respect to the main power supply, and disposed without an element other than wiring between the input capacitor and the driver circuit; With
The driver circuit connects the main power supply to the control terminal via the input impedance element when the switching element is switched from a non-conducting state to a conducting state . The switching element has a control terminal capacitance in which electric charges are accumulated in the control terminal in a conductive state,
The capacitance C ₂ of the input capacitor includes a control terminal capacitance C _gs of the switching element, an intermediate potential V _dr between the driver circuit and the impedance element when the input capacitor is sufficiently charged, and the The switching element driving device according to claim 8 , wherein the switching element driving device satisfies the relationship of the following expression 3 with respect to the ON threshold voltage V _th of the switching element.

The impedance element is a resistor, and the resistance value R ₂ [Ω] of the resistor is a capacitance C ₂ [F] of the input capacitor, and a carrier frequency f of a duty signal for driving the switching element on and off. The switching element driving device according to claim 9 , wherein the relationship of the following formula 4 is satisfied with respect to [Hz], duty ratio D, and Napier number e.

The impedance element is a coil, and the self-inductance L [H] of the coil is expressed by the following equation with respect to the capacitance C ₂ [F], the carrier frequency f [Hz], and the duty ratio D of the input capacitor. The switching element driving device according to claim 9 , wherein the relationship 5 is satisfied.

It has another input capacitor (11) connected in parallel with the impedance element and the input capacitor with respect to the main power supply, and arranged without an element other than wiring between the impedance element. The switching element driving device according to any one of claims 8 to 11 .

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