JP6331200B2 - Ultrasound gridded three-dimensional electrified imaging device - Google Patents

Description

  The present invention relates to an image acquisition device, which transmits an acoustic signal in water such as the sea and acquires a three-dimensional image of a wide space by a reflected wave from the object regardless of the turbidity or illuminance of water. The present invention relates to an imaging apparatus.

  In order to realize three-dimensional imaging, it is basically necessary to arrange electrodes two-dimensionally in a matrix, and in order to realize a high-resolution device, a large number (about 10,000) of electrodes are required and put into practical use. Is extremely difficult.

  Therefore, the inventor has a three-dimensional imaging method that includes a one-dimensional array of transmitters that sweep and radiate ultrasonic waves in different directions for each frequency, and a receiver that is one-dimensionally divided in a direction orthogonal to the sweep direction. We are developing.

  However, according to this method, a two-dimensional convergent acoustic lens having a convergence characteristic in the two-dimensional direction is required, and the two-dimensional convergent acoustic lens becomes a heavy object, and thus it is difficult to simplify the apparatus.

  Therefore, the present invention provides a configuration method that does not require a two-dimensional converging acoustic lens in a method in which a one-dimensional direction is scanned by a frequency and three-dimensional imaging is performed by a one-dimensional array of receivers.

  Various methods for performing three-dimensional imaging by sweeping and irradiating ultrasonic waves in different directions for each frequency are known.

  A first known example of such a method is a method of imaging a three-dimensional space using a frequency steering type two-dimensional acoustic array disclosed in Patent Document 1.

  The simplest configuration of the two-dimensional acoustic array in this known example is the frequency steering type two-dimensional array 1 shown in FIG. 1, and includes an acoustic transducer element 2, a signal electrode 3, a first wiring 4, a second wiring 5, and a ground. It consists of an electrode 6 and a signal terminal 7.

  However, even in the simplest configuration shown in FIG. 1, it is necessary to arrange a large number (UxV) of signal electrodes 3 in a two-dimensional (matrix) form. In a high-resolution apparatus, 10,000 (U: 100, V: It is difficult to put this method to practical use.

  FIG. 2 shows a second known example by a method of sweeping and irradiating ultrasonic waves in different directions for each frequency. This method is the method shown in Patent Document 2 by the inventors.

  The transmitter 8 in FIG. 2 transmits ultrasonic waves having different frequencies for each direction, and the simplest configuration method of the transmitter 8 is shown in Patent Document 3 which is a known technique by the inventors.

  As shown in FIG. 4, this known transmitter 8 includes a pair of ground electrodes 22 and signal electrodes as common electrodes on both surfaces of piezoelectric elements 20 formed by alternately reversing polarization axis directions 21. 23 is formed.

  When one drive signal 25 is applied between the ground electrode 22 and the signal electrode 23, the ultrasonic wave front 26 is radiated in different directions in the propagation medium 9 according to the signal frequency, and the target region 10 is moved along the x axis. Sweep scan in direction.

  The ultrasonic wavefront 26 is a fan-shaped ultrasonic beam 13 that is narrow in the x-axis direction and wide in the z-axis direction because the shape of the transmitter 8 is a rod.

  Here, the direction in which the ultrasonic wavefront 26 propagates is referred to as an ultrasonic wavefront radiation direction 24, and hereinafter, the angle at which the ultrasonic wavefront 26 is inclined with respect to the x-axis (arrangement direction of the transmitter 8) is defined as θ. An angle inclined with respect to the axis (assumed to be vertical) is assumed to be ψ.

  The principle of operation of the transmitter 8 is as shown in FIG. 5. When a sine wave drive signal 25 is applied between the ground electrode 22 and the signal electrode 23, a wavefront indicated by an arc in FIG. 5 is formed (solid line and broken line). The phase of adjacent wavefronts at the same time are inverted, so that the radiated sound wave is canceled out in the normal direction of the transmitter 8 and the ultrasonic wavefront radiation is in the inclined direction. An ultrasonic beam is formed in the direction 24.

  In FIG. 5, when the frequency is high, since the wavelength is short, the high-frequency transmission wavefront 27 is formed in the vicinity of the front surface as shown in a) of FIG. On the other hand, when the frequency is low, since the wavelength is long, the low-frequency transmission wavefront 28 is formed in a more inclined direction as shown in FIG.

Assuming that the transducer pitch is d ₀ and the wavelength of the drive signal is λ, the angle θ ₀ at which the sound wave is radiated is expressed by Equation 1.

(Equation 1)
θ ₀ = sin ⁻¹ {λ / (2d ₀ )}
Further, assuming that the number of elements is N, the long-distance sound field directivity characteristic R (θ) in the θ direction is expressed by Formula 2.

(Equation 2)
R (θ) = sin {0.5N (η−γ ₀ )} / sin {0.5 (η−γ ₀ )}
η = π, γ ₀ = 2πd ₀ sin (θ) / λ

On the other hand, the reflected sound wave 14 from the object 15 is detected in a one-dimensional array in which electrodes are divided in the z-axis direction (vertical direction) shown in FIG. An image is formed on the surface 12 to become an object image 17.

  The wave detection surface 12 is made of a piezoelectric material, and converts incident sound pressure into an electric signal on the dividing element 16.

  Here, two objects (not shown) have the same angle ψ (elevation angle) tilted with respect to the z-axis direction and have different angles θ (azimuth angles) tilted with respect to the x-axis direction. Then, the reflected wavefronts from these objects are defined as a high-frequency reception wavefront 29 and a low-frequency reception wavefront 30 in a) of FIG.

  Since the high-frequency reception wavefront 29 and the low-frequency reception wavefront 30 have the same angle ψ that is inclined with respect to the z-axis direction, as shown in FIG. The light is converged on the same dividing element 16 on the wave receiving detection surface 12 and converted into an output signal 18 from the single dividing element 16.

  In the configuration of FIG. 2, the frequency of the irradiated signal varies depending on the orientation θ (the angle inclined with respect to the x-axis direction) of the object 10, and therefore the horizontal position of the object 10 is shown in FIG. 3. Thus, it is known from the signal frequency component intensity 19 in the element output signal 18.

  On the other hand, two objects (not shown) have the same angle θ (azimuth angle) inclined with respect to the x-axis direction, but have different angles ψ (elevation angle) inclined with respect to the z-axis direction. Then, the reflected wavefronts from these objects are respectively referred to as an upper reception wavefront 31 and a lower reception wavefront 32 in FIG.

  Since the upper reception wavefront 31 and the lower reception wavefront 32 have different angles ψ inclined with respect to the z-axis direction, element positions that are different positions of the dividing element 16 on the wave reception detection surface 12, respectively. 33 or the element position 34 converges.

  Therefore, the elevation angle (angle ψ) to the object is known as the position of the dividing element 16 where the signal appears on the one-dimensional array receiving detection surface 12, and information about the inclination angle with respect to the x-axis direction and the z-axis direction is provided. The two-dimensional shape of the object 15 is known from (θ, ψ).

  Further, since the distance to the object 15 (y-axis direction) is known from the round-trip time of the ultrasonic wave, the shape of the measurement object in the three-dimensional space is completely grasped by these three pieces of information.

  As described above, in the method of FIG. 2, all the acoustic signals from the respective reflection points incident on the receiving two-dimensional convergent acoustic lens 11 are added in the same phase on the one-dimensional array receiving detection surface 12. The highest sensitivity achievable as a device will be realized.

  However, from such an operating principle, in the conventional method of FIG. 2, the two-dimensional convergent acoustic lens 11 having a convergence characteristic in the two-dimensional direction is an indispensable constituent requirement.

  Here, in the configuration using such a two-dimensional converging acoustic lens, it is necessary to increase the diameter of the lens in order to achieve high sensitivity, and in order to reduce the area of the one-dimensional array receiving / detecting surface 12, it is necessary to shorten the lens. Focusing is also necessary.

  Due to these requirements, the acoustic lens inevitably becomes thick and increases in weight, so that it is difficult to simplify the apparatus using the conventional method shown in FIG.

Special table 2007-535195 Japanese Examined Patent Publication No. 52-47697 JP 47-26160 A JP 2010-71967 A

The Ocean Acoustics Society "Basics and Applications of Ocean Acoustics" Naruyamado Shoten 2004

  The present invention provides a three-dimensional imaging method that does not require a two-dimensional convergent acoustic lens that is a heavy object.

  The present invention provides a three-dimensional imaging system that does not require a two-dimensional convergent acoustic lens by using a one-dimensional array of transmitters and a one-dimensional array of receivers in a configuration that scans in a one-dimensional direction according to frequency.

Specifically, an ultrasonic three-dimensional measurement apparatus according to the present invention includes a transmitter in which acoustic transducer elements are arranged in a one-dimensional direction, and a receiver in which receiving elements are arranged in a direction orthogonal to the transmitter arrangement axis direction. A transmitter, a driving signal of the transmitter, and a signal processing unit, and the transmitter is arranged in a three-dimensional space centered on a front direction orthogonal to the transmitter array axis direction. By emitting ultrasonic waves having different irradiation frequencies corresponding to the azimuth angle with respect to the wave array axis, the signal processing unit performs in-phase addition and frequency analysis of the received signal by the wave receiver, thereby transmitting the wave transmitter And an ultrasonic three-dimensional measuring apparatus that obtains azimuth information about each arrangement direction of the receiver and uses the ultrasonic propagation time from the application time of the drive signal to the reception signal incident time to the receiver as distance information in the wave transmitter comprises a front viewing arrangement, the It emits a high frequency component of the drive signals near the front direction including the front by a surface observation configuration, characterized by emitting a low-frequency component of the drive signal to the peripheral direction.

In the ultrasonic three-dimensional measurement apparatus according to the present invention, the ultrasonic radiation azimuth from the transmitter at a specific drive signal frequency is limited to a single azimuth direction with respect to the transmitter array axis. It is preferable.
In the ultrasonic three-dimensional measurement apparatus according to the present invention, it is preferable that the ultrasonic radiation direction from the transmitter with a specific drive signal frequency decreases according to the angle from the front direction.
In the ultrasonic three-dimensional measurement apparatus according to the present invention, it is preferable that the transmitter and the receiver share a part.
Another ultrasonic three-dimensional measuring apparatus according to the present invention includes a transmitter in which sound and a transducer element are arranged in a one-dimensional direction, and a receiver in which a receiving element is arranged in a direction orthogonal to the transmitter arrangement axis direction. A transmitter, a driving signal of the transmitter, and a signal processing unit, and the transmitter is arranged in a three-dimensional space centered on a front direction orthogonal to the transmitter array axis direction. The ultrasonic wave having different irradiation frequencies is emitted corresponding to the azimuth angle with respect to the wave array axis, and the signal processing unit performs in-phase addition and frequency analysis of the received signal by the receiver, thereby transmitting the wave Direction information about each arrangement direction of the detector and the receiver, and ultrasonic three-dimensional measurement using the ultrasonic propagation time from the application time of the drive signal to the reception signal incident time to the receiver as distance information In the apparatus, with respect to the transmitter arrangement direction, There characterized wider than the width of the receivers.
Another ultrasonic three-dimensional measuring apparatus according to the present invention includes a transmitter in which sound and a transducer element are arranged in a one-dimensional direction, and a receiver in which a receiving element is arranged in a direction orthogonal to the transmitter arrangement axis direction. A transmitter, a driving signal of the transmitter, and a signal processing unit, and the transmitter is arranged in a three-dimensional space centered on a front direction orthogonal to the transmitter array axis direction. The ultrasonic wave having different irradiation frequencies is emitted corresponding to the azimuth angle with respect to the wave array axis, and the signal processing unit performs in-phase addition and frequency analysis of the received signal by the receiver, thereby transmitting the wave Direction information about each arrangement direction of the detector and the receiver, and ultrasonic three-dimensional measurement using the ultrasonic propagation time from the application time of the drive signal to the reception signal incident time to the receiver as distance information In the apparatus, the transmitter in the arrangement direction of the receiver Width being narrower than the width of the receivers.
Further, in the ultrasonic three-dimensional measurement apparatus according to the present invention, the transmitter has a front observation configuration, and the front observation configuration radiates a high-frequency component of the drive signal in the vicinity of the front including the front, It is preferable to radiate the low frequency component of the drive signal in the edge direction.
In the ultrasonic three-dimensional measurement apparatus according to the present invention, the ultrasonic radiation azimuth from the transmitter at a specific drive signal frequency is limited to a single azimuth direction with respect to the transmitter array axis. It is preferable.
In the ultrasonic three-dimensional measurement apparatus according to the present invention, it is preferable that the ultrasonic radiation direction from the transmitter with a specific drive signal frequency decreases according to the angle from the front direction.
In the ultrasonic three-dimensional measurement apparatus according to the present invention, it is preferable that the transmitter and the receiver share a part.

  According to the present invention, a two-dimensional convergent acoustic lens that is a heavy object is not required, and the ultrasonic imaging apparatus for three-dimensional imaging can be reduced in size and weight.

Explanatory drawing which shows the frequency steering type two-dimensional array in a well-known example. Explanatory drawing which shows a 2nd well-known example. Explanatory drawing which showed the received wave detection surface by a 2nd well-known example. Explanatory drawing which showed the transmitter by the 2nd well-known example. Explanatory drawing which showed the principle of operation of the transmitter by a 2nd well-known example. Explanatory drawing which showed the condition of the transmission / reception wave front by a 2nd well-known example. Explanatory drawing which showed the structure of the single phase plate. Example 1 Explanatory drawing which showed the whole structure regarding (theta) direction operation | movement. Explanatory drawing which showed the condition where the same phase position of a reflected wave front corresponds with a piezoelectric material presence position. Explanatory drawing which showed the whole structure regarding the (psi) direction operation | movement. Explanatory drawing which showed the condition where the incident time to a single phase element changes according to a z-axis direction position. explanatory view showing a situation of receiving the unwanted wave from two directions of r _2, r ₃ in addition to r ₁ direction. Explanatory drawing which showed the structure of the inversion phase plate. (Example 2) Explanatory drawing which showed the condition where the phase of a received wave front and the polarization axis direction of inversion polarization | polarized_light always correspond. explanatory view showing a situation of receiving the unwanted wave from the r ₂ directions other than r ₁ direction. Explanatory drawing which showed the structure which forms a longitudinally long transmission irradiation wavefront with an inversion phase plate. Explanatory drawing which showed the structure which forms a narrow irradiation wavefront with an inversion phase plate. Explanatory drawing which shows the structure of the single phase plate by attenuation | damping. (Example 3) Explanatory drawing which shows the structure of the single phase plate by scattering. Explanatory drawing which showed the structure of the single phase plate by a ground electrode. Explanatory drawing which showed the structure of the inversion phase plate by transmission. Example 4 Explanatory drawing which showed the structure of the inversion phase plate of the plane structure by transmission. Explanatory drawing which showed the structure of the inversion phase plate of the structure by scattering. Explanatory drawing which showed the structure of the unidirectionalization of the transmission beam by a 90 degree | times phase element. (Example 5) Explanatory drawing which showed unidirectionalization of the transmission / reception wave by a high impedance vertical reflection wall. (Example 6) Explanatory drawing which showed unidirectionalization of the transmission / reception wave by an orthogonal arrangement | positioning polarization plate. Explanatory drawing which showed unidirectionalization of the transmission / reception wave by a low impedance vertical reflection wall. Explanatory drawing which showed the front observation structure by an inclined reflecting plate. (Example 7) FIG. 3 is an explanatory diagram of a three-dimensional overall arrangement of a wave receiving configuration using an inclined reflector. Explanatory drawing which showed the front observation structure by a refractive structure. (Example 8) Explanatory drawing which showed the operating characteristic of the single transmitter. Explanatory drawing which showed the operation | movement and problem of a division | segmentation transmitter. Explanatory drawing which showed the structure which transmits with a division | segmentation transmitter and receives with an inversion phase plate. Example 9 Explanatory drawing which showed the structure by a one-dimensional convergence acoustic lens. (Example 10)

  Various configurations that can eliminate the need for a two-dimensional convergent acoustic lens will be described in detail below by way of examples.

  In the first embodiment according to the present invention, the use of a single phase plate 38 shown in FIG. 7 makes it possible to eliminate the need for a two-dimensional convergent acoustic lens.

  The single phase plate 38 is regarded as a configuration in which the single phase elements 39 shown in FIG. 7 are arranged in the z-axis direction, and the ground electrode 43 is formed in common on the entire back surface of the single phase plate 38.

  Here, in the single phase element 39, the piezoelectric material 40 and the non-piezoelectric material 41 are alternately arranged, and the piezoelectric material 40 is commonly connected to be a signal electrode 42. The signal electrode 42 has a signal terminal 44, and is polarized. As indicated by the arrow in the axial direction 21, the polarization axes of the piezoelectric material 40 are aligned in the same direction.

FIG. 8 shows the overall configuration of the present embodiment relating to the operation in the θ direction. In the present embodiment, the horizontal axis (x-axis direction in FIG. 7) of the single phase plate 38 is arranged in parallel with the center axis (x-axis) of the transmitter 8. Further, the arrangement interval d ₁ of the single phase elements 39 shown in FIG. 7 is configured to coincide with the element interval d ₀ of the transmitter 8.

  In such a configuration, the irradiation direction θ is changed by changing the drive signal frequency of the transmitter 8, and the high-frequency transmission wavefront 27 and the low-frequency transmission wavefront 28 shown in FIG. 8 are transmitted.

  Here, similarly to a) of FIG. 6, two objects (not shown) have the same angle ψ (elevation angle) inclined with respect to the z-axis direction and are inclined with respect to the x-axis direction. Assuming that θ (azimuth angles) exist in different directions, the reflected wavefronts from these objects are a high-frequency reception wavefront 29 and a low-frequency reception wavefront 30 in FIG.

As shown in FIG. 9, the high-frequency reception wavefront 29 and the low-frequency reception wavefront 30 have a horizontal axis of the single phase plate 38 and a center axis (x-axis) of the transmitter 8 that are parallel to each other. Since the arrangement interval d ₁ of the elements 39 and the arrangement interval d _{0 of the} transmitting elements are the same, the same phase position of the reception wavefront always matches the position of the piezoelectric material 40 in the single phase element 39.

  For this reason, the single phase element 39 always converts only the same phase portion of the incident wavefronts 29 and 30 into an electric signal, and the received signal can be received with respect to the wavefront incident from any angle θ (azimuth angle). Are automatically added to the same phase and output to the signal terminal 44.

  Therefore, by using the single phase element 39, the directivity synthesis process relating to the angle θ (azimuth angle) direction becomes unnecessary.

  On the other hand, FIG. 10 shows the overall configuration of the present embodiment regarding the ψ direction operation.

In FIG. 10, two objects (not shown) corresponding to b) in FIG. 6 are inclined with respect to the z-axis direction at the same angle (θ ₁ ) with respect to the x-axis direction. Assuming that the angles are present in different directions (ψ ₁ and ψ ₂ ), the reflected wavefronts from these objects by the irradiation wavefront 46 are respectively the upper reception wavefront 47 (ψ ₁ ) and the front reception wavefront 48 (ψ ₂ = 0). And

Here, since the upper reception wavefront 47 is inclined by the angle ψ _{1 with} respect to the z-axis direction, as shown in FIG. 11, the time of incidence on the single phase element 39 depends on the position in the z-axis direction. Change.

  For this reason, in order to perform in-phase addition, directivity synthesis processing in the z-axis direction is required for V signals from the single phase plate 38.

This directivity synthesis process is described in detail in Non-Patent Document 1. As an example, in the vertical directivity synthesis unit 37 shown in FIG. 11, the delay time terminal 50 of the delay circuit 49 is connected to the inclination angle ψ of the upper reception wavefront 47. By selecting corresponding to ₁ , the time difference or phase difference of the signal in the received signal 51 is compensated, and the compensated signal is added in the same phase.

By this directivity synthesis processing, the upper reception wavefront 47 inclined by the angle ψ ₁ is output as the upper reception output 52, and the front reception wavefront 48 is output independently as the front reception output 53.

  Therefore, the two-dimensional shape of the object 15 is known from the tilt angle information (θ, ψ) with respect to the x-axis direction and the z-axis direction.

  In addition, since the distance to the object 15 (y-axis direction) is known from the round-trip time of the ultrasonic wave, the shape of the measurement object in the three-dimensional space is completely grasped by these three pieces of information. The three-dimensional imaging which does not require an acoustic lens is realized by the single-phase plate 38 of the one-dimensional arrangement.

  The above processes are all in-phase signal addition, and are received from various positions in the horizontal direction (x-axis direction) and the vertical direction (z-axis direction), the high-frequency reception wavefront 29, the low-frequency reception wavefront 30, All of the upper reception wavefront 47 and the front reception wavefront 48 are subjected to the same phase addition and output as maximum reception signals 52 and 53.

  However, according to the single phase plate 38 shown in FIG. 7, half of the receiving area is non-piezoelectric, and the sound wave incident on this portion does not contribute to sensitivity.

Further, in the case of a single phase element 39, as shown in a) of Figure 12, since the wavefront is also in phase addition from the front direction (r ₃ direction), ultrasonic wave from r ₁ a target direction In addition to the wavefront 26, the unnecessary wavefront 54 and the front unnecessary wavefront 55 are received from a total of two directions, r ₂ and r ₃ .

Here, by using the wave transmitter 8, the effect of the polarization axis reversed, as shown in b) of Figure 12, since the to r ₃ direction causes the front unwanted wavefront 55 does not radiate, to r ₂ direction Only the unnecessary wavefront 54 which is an unnecessary response becomes a problem.

Therefore, single phase plate 38 and, in the arrangement according transmitters 8, it is necessary means for suppressing unwanted response to r ₂ directions, unnecessary radiation suppression to r ₂ direction, the sound absorption walls It is realized by various methods described below, such as installation.

  The delay circuit 49 in the vertical directivity synthesis unit 37 is easily realized by a normal analog delay line or a combination of an A / D converter and a digital memory.

  According to the single phase plate 38 shown in FIG. 7, half of the receiving area is non-piezoelectric, and the sound wave incident on this portion becomes invalid and does not contribute to the received signal intensity.

  Therefore, in the second embodiment according to the present invention, an inversion phase plate 56 shown in FIG. 13 is used.

  The inversion phase plate 56 is regarded as a configuration in which the inversion phase elements 57 are arranged in the z-axis direction, and the ground electrode 43 is commonly formed on the entire back surface of the inversion phase plate 56.

  Here, the inversion phase element 57 uses an inversion polarization piezoelectric material 58 in which the polarization axis directions 21 are alternately inverted, and the inversion polarization piezoelectric material 58 is commonly connected to form a signal electrode 42, and the signal electrode 42 is a signal terminal. 44.

In the imaging method using the inverting phase plate 56 of the present embodiment, as shown in FIG. 14, the horizontal axis of the inverting phase plate 56 is arranged in parallel with the center axis (x axis) of the transmitter 8, The polarization axis inversion period d ₂ of the inversion phase element 57 is configured to match the element interval d ₀ of the transmitter 8.

  In such a configuration, by changing the driving signal frequency of the transmitter 8, the irradiation direction θ is changed, and the high-frequency transmission wavefront 27 and the low-frequency transmission wavefront 28 shown in FIG. The reflected wave from the object is received by the inversion phase plate 56.

  Here, similarly to a) of FIG. 6, two objects (not shown) have the same angle ψ (elevation angle) inclined with respect to the z-axis direction and are inclined with respect to the x-axis direction. Assuming that θ (azimuth angles) exist in different directions, the reflected wavefronts from these objects are defined as a high-frequency reception wavefront 29 and a low-frequency reception wavefront 30 in FIG.

In these high-frequency reception wavefront 29 and low-frequency reception wavefront 30, the horizontal axis of the single phase plate 38 and the center axis (x-axis) of the transmitter 8 are parallel, and the arrangement interval d ₁ of the single phase elements 39. 14 and the arrangement interval d _{0 of the} transmission elements are the same, as shown in FIG. 14, the phases of the high-frequency reception wavefront 29 and the low-frequency reception wavefront 30 and the inversion polarization piezoelectric material 58 of the inversion phase element 57 The polarization axis direction 21 always matches.

  For this reason, the single phase element 39 always inverts the opposite phase portions of the high-frequency reception wavefront 29 and the low-frequency reception wavefront 30 and converts them all into electrical signals having the same phase.

  Therefore, the inverting phase element 57 automatically adds the received signals in the same phase for any wavefront incident from any angle θ (azimuth angle) and outputs it to the signal terminal 44.

  For this reason, by using the inverting phase element 57, directivity synthesis processing in the direction of the angle θ (azimuth angle) becomes unnecessary.

  On the other hand, with respect to the vertical plane, similarly to FIG. 11, each delay signal 49 of the inverting phase element 57 formed by dividing the inverting phase plate 56 in the z-axis direction is subjected to directivity synthesis processing by the delay circuit 49. Thus, the azimuth resolution in the vertical (ψ) direction is formed.

  Therefore, the two-dimensional shape of the object 15 is known from the information on the inclination angle with respect to the x-axis direction and the z-axis direction (θ, ψ).

  In addition, since the distance to the object 15 (y-axis direction) is known from the round-trip time of the ultrasonic wave, the shape of the measurement object in the three-dimensional space is completely grasped by these three pieces of information. The three-dimensional imaging which does not require an acoustic lens is realized by the single-phase plate 38 of the one-dimensional arrangement.

  Further, in the inversion phase plate 56 shown in FIG. 13, the entire receiving aperture is piezoelectric, and all incident sound waves contribute to the intensity of the received signal.

  Here, the inversion phase element 57 shown in a) of FIG. 15 responds to the ultrasonic wavefront 26 and the unnecessary wavefront 54, and the transmitter 8 by the polarization axis inversion shown in FIG. 26 and the unwanted wavefront 54.

  Therefore, in the case of the configuration in which the inversion phase plate 56 and the transmitter 8 by polarization axis inversion are combined, the unnecessary wavefront 54 is not suppressed, and thus the effect of separately providing the transmitter and the receiver is the single phase plate. It is reduced compared to 38.

  For this reason, in the case of the inversion phase plate 56, the transmission signal source 59 is connected to a part of the signal terminal 44 as shown in FIG. The structure which forms 60 is also possible.

  Furthermore, as shown in FIG. 17, when all the signal terminals 44 on the inverting phase plate 56 are driven by the delay time control by the delay circuit 49, it is possible to form narrow irradiation wavefronts 61 and 62 that are also narrow in the z-axis direction. .

  As described above, in the case of using the inversion phase plate 56, a configuration in which a dedicated wave transmitter is not required by using the inversion phase plate 56 for both transmission and reception is also possible.

In the case of a structure combining wave transmitter 8 and an inverted phase plate 56 due to the polarization axis reversed, as with a), b) in FIG. 15, since the unnecessary wave front 54 of the r ₂ direction remains, r ₂ It is necessary to take measures such as shielding the unwanted wavefront 54 in the direction or unifying the transmission direction in the transmitter 8.

  Various construction methods of the single phase plate will be described with reference to examples.

  The configuration of a single phase plate by attenuation is shown in FIG.

  The attenuation single phase plate 63 shown in FIG. 18 is realized by arranging a sound absorbing material 65 on the piezoelectric material 64.

  According to this configuration, since the antiphase portion is attenuated, in-phase addition is realized. This configuration can also be used as a frequency scanning type transmitter.

  A configuration of a single phase plate by scattering is shown in FIG.

  The scattering single phase plate 66 is realized by disposing a scatterer 67 having an acoustic impedance different from that of the propagation medium 9 on the piezoelectric material 64.

  According to this configuration, since the antiphase wavefront part is backscattered as the scattered signal 45, in-phase addition is realized.

  This configuration can also be used as a frequency scanning type transmitter.

  The configuration of a single phase plate using ground electrodes is shown in FIG.

  The ground electrode single phase plate 68 is realized by disposing an intermittent ground electrode 69 on the piezoelectric material 64 and commonly connecting the intermittent ground electrode 69 by a ground connection 70.

  According to this configuration, since the signal at the position where the intermittent ground electrode 69 exists is output to the signal terminal 44, in-phase addition is realized.

  This configuration can also be used as a frequency scanning type transmitter.

  Various construction methods of the inversion phase plate will be described with reference to examples.

  FIG. 21 shows the configuration of the inversion phase plate by transmission in this example.

  The transmission reversal phase plate 71 has a transmission material 72 disposed intermittently on the piezoelectric material 64.

  Here, the sound velocity of the transmission material 72 is made of a material different from the sound velocity of the propagation medium 9, and a half-wave phase difference is formed between the transmission signal and the direct signal, thereby realizing the same phase addition.

The thickness t of the transmissive material 72 required to form a half-wave phase difference between the two transmitted signals is c _{0 where} the sound velocity in the propagation medium 9 is c ₀ , the sound velocity in the transmissive material 72 is c _1, and c ₁ < Assuming c ₀ , the center frequency of the signal to be used is f ₀ and Equation 3 is obtained.

(Equation 3)
t / c ₁ -t / c ₀ = 1 / (2f ₀ )
f ₀ t (1 / c ₁ -1 / c ₀ ) = 1/2

Here, the wavelength in the propagation medium 9 is λ ₀ (= c ₀ / f ₀ ), the wavelength in the transmission material 72 is λ ₁ (= c ₁ / f ₀ ), and the wavelength ratio is n (= λ ₀ / λ _{If 1} = c ₀ / c ₁ ), Equation 3 becomes Equation 4.

(Equation 4)
t (1 / λ ₁ -1 / λ ₀ ) = 1/2
_{t (λ 0 / λ 1 -1} ) = λ 0/2
t = (1/2) λ ₀ / (n-1)

Here, as a specific example, assuming that c _{0 is} water (1500 m / s), c _{1 is} silicon rubber (1000 m / s), and λ _{0 is} 1 mm (1.5 MHz), t = (1/2) λ ₀ / ( n-1) = (1/2) 1 / (1.5-1) = 1 (mm), and a half-wave phase difference is formed by silicon rubber of about 1 mm.

  This configuration can also be used as a frequency scanning type transmitter.

  As shown in FIG. 22, the transmission plane reversal phase plate 73, which is a plane configuration reversal phase plate by transmission, is configured by alternately arranging a high sound velocity material 74 and a low sound velocity material 75 on a piezoelectric material 64. Then, a half-wave phase difference is formed between the transmitted signals to realize the same phase addition.

In this configuration, the thickness t ′ required to form the half-wave phase difference is such that the sound velocity of the high sonic material 74 is c ₂ , the sound velocity of the low sonic material 75 is c ₁ , the frequency is f _0, and c _{If 1} <c ₂ , Equation 5 is obtained.

(Equation 5)
t '/ c ₁ -t' / c ₂ = 1 / (2f ₀ )
f ₀ t '(1 / c ₁ -1 / c ₂ ) = 1/2

Here, the wavelength in the low acoustic velocity material 75 is λ ₁ (= c ₁ / f ₀ ), the wavelength in the high acoustic velocity material 74 is λ ₂ (= c ₂ / f ₀ ), and the wavelength ratio is n ′ (= λ ₂ / λ ₀ = c ₂ / c ₁ ), Equation 5 becomes Equation 6.

(Equation 6)
t '(1 / λ ₁ -1 / λ ₂ ) = 1/2
_{t '(λ 2 / λλ 1} -1) = λ 2/2
t '= (1/2) λ ₂ / (n-1)

Here, as a specific example, assuming that c _{2 is} epoxy (2500 m / s), c _{1 is} silicon rubber (1000 m / s), and λ _{2 is} 1 mm (2.5 MHz), t ′ = (1/2) λ ₂ / (n-1) = (1/2) 1 / (2.5-1) = 1/3 (mm), and a half-wave phase difference is formed by alternately arranging about 0.3 mm of epoxy and silicon rubber.

  According to this configuration, the surface shape becomes a flat surface, and the reliability during use is improved. At the same time, the thickness of the adhesive material is reduced, and sound wave attenuation in the material is reduced.

  This configuration can also be used as a frequency scanning type transmitter.

  FIG. 23 shows the configuration of an inversion phase plate configured by scattering.

  The scattering inversion phase plate 76 has rod-like high acoustic impedance scatterers 77 and low acoustic impedance scatterers 78 arranged alternately on the piezoelectric material 64 in the x-axis direction to form a planar one-dimensional diffraction grating. .

  Since the scattered wavefronts of such scatterers are alternately phase-inverted and all have the same phase, a scattered parallel plane wave 79 is formed, and the same-phase addition is realized.

  This configuration is not limited to the present embodiment, and a configuration using a backscattered wave in the incident direction or a configuration using a frequency scanning type transmitter is also possible.

  In the configuration using the single phase plate 38 or the inversion phase plate 56, unidirectional transmission beam is indispensable. Here, the unidirectional transmission beam is implemented by the 90 degree phase element as shown in FIG. This will be explained with an example.

  In the present embodiment, only the target ultrasonic wavefront 26 is obtained by using the 90-degree phase element 80 of FIG. 24, which is a known technique disclosed in Patent Document 3 by the inventors, as the transmitter 8. To transmit.

  As shown in FIG. 24, the 90-degree phase element 80 has a first divided signal electrode 81 and a second divided signal electrode 82 in a region in the same polarization axis direction. The drive signal line 84 is commonly connected.

Here, a signal generator (not shown) generates drive signals S ₀ and S ₉₀ having a phase difference of 90 degrees from each other, applies the drive signal S ₀ to the first drive signal line 83, and drives the drive signal. S ₉₀ is applied to the second drive signal line 84.

By the action of the polarization axis reversed this signal application method, from the elements of the 90-degree phase device 80 is transmitting four-phase signals having a phase difference of 90 degrees, the radiation of the unnecessary wave front 54 is unnecessary signal to the r ₂ direction Is suppressed, and only the ultrasonic wavefront 26 in the target direction r ₁ is formed.

Therefore, even in an insufficient reception configuration such as the single phase plate 38 or the inversion phase plate 56 that receives unnecessary signals from other than the target direction at the same time due to the limitation of the device scale, it is 90 as a transmitter. By using the phase element 80, the device for detecting only the reflector in the direction of the target signal r ₁ is completed.

The 90-degree phase element 80 exchanges drive signal connection positions, connects the drive signal S ₉₀ to the first drive signal line 83, and connects the drive signal S ₀ to the second drive signal line 84. r The operation can be changed to transmit in only _two directions.

  In the configuration using the single phase plate 38 or the inversion phase plate 56, unidirectional transmission waves are indispensable. Here, unidirectional transmission / reception by vertical wall reflection will be described with reference to an embodiment.

  In this embodiment, a high-impedance vertical reflection wall 85 made of a material having an acoustic impedance higher than that of the medium 9 shown in FIG. By arranging them orthogonally to each other, the propagation direction of the unnecessary wavefront 54 is inverted, and the in-phase inversion wavefront 35 is used, so that only the synthesis target wavefront 86 can be transmitted.

  According to this configuration, in addition to the mounting element 87, the mirror image element 88 is formed, and the diameter is effectively doubled, so that the resolution is also doubled.

  Here, as shown in FIG. 26, a pair of orthogonally arranged inverted polarization plates 89 and 90 made of a piezoelectric material having an acoustic impedance higher than the acoustic impedance of the medium 9 corresponds to the position A in FIG. When the orthogonal arrangement inversion polarization plate 90 is driven, the orthogonal arrangement inversion polarization plate 89 operates as the high-impedance vertical reflection wall 85 in b) of FIG. 25, and similarly to b) of FIG. Only the single composite target wavefront 86 in FIG. 26 is transmitted, and the effective aperture is almost twice as large as the aperture of the orthogonally arranged reverse polarization plate 90 alone.

  In contrast, in this configuration, when the orthogonally arranged reverse polarization plate 89 is used, it is possible to observe a direction that is symmetric with respect to the front (y ″ axis) direction.

  In addition, by arranging a low impedance vertical reflecting wall 91 made of a material whose acoustic impedance is lower than that of the medium 9 at the intermediate position B of the piezoelectric element 20 in FIG. By reversing and making a reverse phase inversion wavefront 36, only the synthesis target wavefront 86 is transmitted.

  According to this configuration, similarly to FIG. 25, in addition to the mounting element 92, the anti-phase mirror image element 93 is formed, effectively doubling the aperture and doubling the resolution.

  In this case, the acoustic impedance is lower than that of the medium 9, and the vertical reflection wall 91 is reduced in weight.

  This configuration by vertical wall reflection can also be used as a receiver in the present invention.

  Further, this configuration is not limited to the method of the present invention, and can be widely used for other frequency scanning ultrasonic imaging devices such as an acoustic lens method.

  In the normal configuration with the single phase plate 38 or the inverted phase plate 56, the wavefront in the direction greatly inclined with respect to the front direction (y-axis direction) is a target, and the direction near the front cannot be observed.

  Hereinafter, the front observation configuration using the inclined reflector will be described in detail.

  In the present embodiment, by using the inclined reflector 94 shown in FIG. 28, the propagation directions of the reception wavefront 26 and the unnecessary wavefront 54 are converted into a front vicinity wavefront 95 and a front vicinity unnecessary wavefront 96.

Here, the incident angle of the wavefront to be converted is θ _1, and the apex angle ε ₁ of the inclined reflector 94 required to convert the wavefront into the wavefront from the front direction is given by Equation 7. .

(Equation 7)
ε ₁ = (π / 4-θ ₁ ) / 2

  FIG. 29 shows a three-dimensional overall arrangement of a wave receiving configuration using the inclined reflector 94.

  This operation is the same also in the transmission, and if the 90-degree phase element 80 in FIG. Thus, selective transmission with respect to the left and right visual fields in the vicinity of the front direction becomes possible.

  In the normal configuration with the single phase plate 38 or the inverted phase plate 56, the wavefront in the direction greatly inclined with respect to the front direction (y-axis direction) is targeted, and the front direction cannot be observed.

Hereinafter, according to the present embodiment, a front observation configuration using a refractive structure will be described in detail.

  In the present embodiment, by using the refractive structure 97 shown in FIG. 30, the propagation directions of the reception wavefront 26 and the unnecessary wavefront 54 are converted into a front vicinity wavefront 95 and a front vicinity unnecessary wavefront 96.

Here, the incident angle of the wavefront to be converted is θ _1, and the apex angle ε ₂ of the refractive structure 97 for converting the wavefront into the wavefront from the front direction is the sound velocity in the propagation medium 9 c ₀ , The speed of sound in the refractive structure 97 is c ₁ and the relationship of Equation 8 is established.

(Equation 8)
(π / 4-α) + ε ₂ = θ ₁
sinα / sinε ₂ = c ₁ / c ₀

From the relationship of Equation 8, the apex angle ε ₂ of the refractive structure 97 is given by the root of Equation 9.

(Equation 9)
^{_{ε 2 -sin -1 (c 1 sinε}} 2 / c 0) = θ 1 -π / 4

  Also in the transmission, such a refracting structure 97 can similarly transmit in the direction near the front.

  Further, when the 90-degree phase element 80 of FIG. 24 is used instead of the inversion phase plate 56, unidirectional transmission is performed, and therefore selective transmission can be performed with respect to the left and right visual fields near the front direction.

  In the frequency scanning method, improvement of distance resolution is a problem.

  In the present embodiment, a split transmitter, which is a known technique disclosed in Patent Document 4 by the inventors, is used. The combined use of this divided transmitter and the single phase plate 38 or the inverted phase plate 56 improves the distance resolution.

When a single transmitter 8 shown in a) of FIG. 31 is driven by a drive signal 98 having a wave number of half or more of the number of polarization sections, the directivity characteristic shown in b) of FIG. Since the drive signal 98 is used, the distance resolution is reduced.

  Therefore, for example, as shown in a) of FIG. 32, when the transmitter 8 is divided into two to form the divided transmitter 99, the required wave number of the divided drive signal 100 is halved and the distance resolution is doubled.

  However, in this configuration, unnecessary responses r ′, r ″ and the like shown in FIG. 32 b appear due to unnecessary wavefronts shown as r ′, r ″ in FIG. 32 a, and the directivity characteristics deteriorate.

Therefore, in the present invention, as an example, as shown in a) of FIG. 33, the transmission is performed by the division transmitter 99 and is received by the inverting phase plate 56, and the width W _U ′ of the inverting phase plate 56 is set. And the single divided aperture width W _U in the divided transmitter 99.

  The directivity by the configuration shown in FIG. 33 a) is a product of the transmission directivity and the reception directivity in the azimuth resolution, so that the unnecessary response is suppressed and the good characteristic shown in b) of FIG. 33 is obtained. .

  As described above, the configuration in which the wave is transmitted by the divided transmitter 99 and received by the single phase plate 38 or the inverted phase plate 56 can improve the distance resolution while maintaining a high azimuth resolution.

  In addition, since the azimuth resolution is the product of the transmission directivity and the reception directivity, the configuration of a planar receiver and a rod-shaped transmitter generally increases the diameter of the transmitter. The improvement of the azimuth resolution by this is advantageous in terms of the device configuration.

  In the present embodiment, as shown in FIG. 34, by using a one-dimensional convergent acoustic lens 101 having a convergence characteristic only in a direction orthogonal to the frequency scanning direction, the upper reception wavefront 47 and the front reception wavefront 48 are Since the angle ψ tilted with respect to the z-axis direction is different, the upper reception output 52 and the front reception output 53 are output separately.

  For this reason, the vertical directivity synthesis unit 37 becomes unnecessary.

  Here, assuming a normal rectangular opening, the thickness of the one-dimensional convergent acoustic lens 101 is half that of the two-dimensional convergent acoustic lens 11, and the weight can be reduced.

  In the above embodiment, the incident wave is described as a plane wave assuming that the object is far away, but since a spherical wave from an object existing in the vicinity can also be converted into a plane wave by using a two-dimensional convergent acoustic lens, Those skilled in the art can easily understand that the present invention is not limited to such an embodiment but can be applied to high-resolution imaging of a near object.

  Further, in the embodiment shown in FIG. 11, the selection position of the delay time terminal 50 in the vertical directivity synthesis unit 37 is linear, but the present invention is not limited to such an embodiment, and the selection position is changed. It can be easily understood by those skilled in the art that the concave surface can be applied to high-resolution imaging of a near object by using it together with a one-dimensional convergent acoustic lens.

  According to the present invention, three-dimensional imaging using ultrasound is realized by a simple device.

DESCRIPTION OF SYMBOLS 1 Frequency steering type two-dimensional array 2 Acoustic transducer element 3 Signal electrode 4 1st wiring 5 2nd wiring 6 Ground electrode 7 Signal terminal 8 Transmitter 9 Propagation medium 10 Target area 11 Two-dimensional convergent acoustic lens 12 One-dimensional array receiving Detection surface 13 Fan-shaped ultrasonic beam 14 Reflected sound wave 15 Object 16 Dividing element 17 Object image 18 Element output signal 19 Signal frequency component intensity 20 Piezoelectric element 21 Polarization axis direction 22 Ground electrode 23 Signal electrode 24 Ultrasonic wavefront radiation direction 25 Drive signal 26 Ultrasonic wavefront 27 High frequency transmission wavefront 28 Low frequency transmission wavefront 29 High frequency reception wavefront 30 Low frequency reception wavefront 31 Upper reception wavefront 32 Lower reception wavefront 33 Element position 34 Element position 35 In-phase inversion wavefront 36 Reverse phase inversion wavefront 37 Vertical pointing Synthetic unit 38 Single phase plate 39 Single phase element 40 Piezoelectric material 4 Non-piezoelectric material 42 Signal electrode 43 Ground electrode 44 Signal terminal 45 Scattered signal 46 Irradiation wavefront 47 Upper reception wavefront 48 Front reception wavefront 49 Delay circuit 50 Delay time terminal 51 Reception signal 52 Upper reception output 53 Front reception output 54 Unwanted wavefront 55 Front Unnecessary wavefront 56 Inverted phase plate 57 Inverted phase element 58 Inverted polarization piezoelectric material 59 Transmission signal source 60 Partially transmitted irradiation wavefront 61 Narrow irradiation wavefront 62 Narrow irradiation wavefront 63 Attenuating single phase plate 64 Piezoelectric material 65 Sound absorbing material 66 Scattering single phase Plate 67 Scatterer 68 Ground electrode single phase plate 69 Intermittent ground electrode 70 Ground connection 71 Transmission reversal phase plate 72 Transmission material 73 Transmission plane reversal phase plate 74 High sound speed material 75 Low sound speed material 76 Scattering reversal phase plate 77 High acoustic impedance Scatterer 78 Low acoustic impedance scatterer 79 Scattered parallel plane wave 8 0 90 degree phase element 81 1st divided signal electrode 82 2nd divided signal electrode 83 1st drive signal line 84 2nd drive signal line 85 High impedance vertical reflection wall 86 Synthetic target wavefront 87 Mounting element 88 Mirror image element 89 Orthogonal arrangement inversion polarization Plate 90 Orthogonal arrangement inversion polarization plate 91 Low impedance vertical reflection wall 92 Mounting element 93 Mirror image element 94 Inclined reflection plate 95 Front near wavefront 96 Front near unnecessary wavefront 97 Refraction structure 98 Drive signal 99 Divided transmitter 100 Divided drive signal 101 1 Dimensional convergence acoustic lens

Claims (10)

A transmitter in which acoustic transducer elements are arranged in a one-dimensional direction; a receiver in which wave receiving elements are arranged in a direction orthogonal to the transmitter arrangement axis direction; a drive signal for the transmitter; and a signal processing unit; Have
The transmitter radiates ultrasonic waves having different irradiation frequencies corresponding to the azimuth angle with respect to the transmitter array axis, in a three-dimensional space centered on the front direction orthogonal to the transmitter array axis direction,
The signal processing unit performs in-phase addition and frequency analysis of the received signal by the receiver to obtain azimuth information related to each arrangement direction of the transmitter and the receiver,
In the ultrasonic three-dimensional measurement apparatus using the ultrasonic propagation time from the application time of the drive signal to the reception signal incident time to the receiver as distance information,
The transmitter has a front observation configuration , and the front observation configuration radiates a high frequency component of the drive signal in the vicinity of the front including the front, and radiates a low frequency component of the drive signal in a marginal direction. Ultrasonic three-dimensional measuring device characterized by The ultrasonic three-dimensional measurement apparatus according to claim 1,
An ultrasonic three-dimensional measurement apparatus, wherein an ultrasonic radiation direction from the transmitter at a specific drive signal frequency is limited to a single azimuth direction with respect to the transmitter array axis.   The ultrasonic three-dimensional measurement apparatus according to claim 1,
  The ultrasonic three-dimensional measuring apparatus, wherein the ultrasonic radiation azimuth from the transmitter at a specific drive signal frequency decreases according to an angle from the front direction.   The ultrasonic three-dimensional measurement apparatus according to claim 1,
  The ultrasonic three-dimensional measurement apparatus, wherein the transmitter and the receiver share a part.   A transmitter in which acoustic transducer elements are arranged in a one-dimensional direction, a receiver in which wave receiving elements are arranged in a direction orthogonal to the transmitter arrangement axis direction, a drive signal for the transmitter, and a signal processing unit And
  The transmitter radiates ultrasonic waves having different irradiation frequencies corresponding to the azimuth angle with respect to the transmitter array axis, in a three-dimensional space centered on the front direction orthogonal to the transmitter array axis direction,
  The signal processing unit performs in-phase addition and frequency analysis of the received signal by the receiver, thereby obtaining azimuth information relating to each arrangement direction of the transmitter and the receiver,
  In the ultrasonic three-dimensional measurement apparatus using the ultrasonic propagation time from the application time of the drive signal to the reception signal incident time to the receiver as distance information,
  An ultrasonic three-dimensional measurement apparatus characterized in that a width of the transmitter with respect to the transmitter arrangement direction is wider than a width of the receiver.   A transmitter in which acoustic transducer elements are arranged in a one-dimensional direction, a receiver in which wave receiving elements are arranged in a direction orthogonal to the transmitter arrangement axis direction, a drive signal for the transmitter, and a signal processing unit And
  The transmitter radiates ultrasonic waves having different irradiation frequencies corresponding to the azimuth angle with respect to the transmitter array axis, in a three-dimensional space centered on the front direction orthogonal to the transmitter array axis direction,
  The signal processing unit performs in-phase addition and frequency analysis of the received signal by the receiver, thereby obtaining azimuth information relating to each arrangement direction of the transmitter and the receiver,
  In the ultrasonic three-dimensional measurement apparatus using the ultrasonic propagation time from the application time of the drive signal to the reception signal incident time to the receiver as distance information,
  An ultrasonic three-dimensional measurement apparatus, wherein a width of the transmitter with respect to an arrangement direction of the receiver is narrower than a width of the receiver.   The ultrasonic three-dimensional measurement apparatus according to claim 5 or 6,
  The transmitter has a front observation configuration, and the front observation configuration radiates a high frequency component of the drive signal in the vicinity of the front including the front, and radiates a low frequency component of the drive signal in a marginal direction. An ultrasonic three-dimensional measuring apparatus characterized by the above.   The ultrasonic three-dimensional measurement apparatus according to claim 7,
  An ultrasonic three-dimensional measurement apparatus, wherein an ultrasonic radiation direction from the transmitter at a specific drive signal frequency is limited to a single azimuth direction with respect to the transmitter array axis.   The ultrasonic three-dimensional measurement apparatus according to claim 7,
  The ultrasonic three-dimensional measuring apparatus, wherein the ultrasonic radiation azimuth from the transmitter at a specific drive signal frequency decreases according to an angle from the front direction.   The ultrasonic three-dimensional measurement apparatus according to claim 7,
  The ultrasonic three-dimensional measurement apparatus, wherein the transmitter and the receiver share a part.