JP6089677B2 - Power supply - Google Patents
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- JP6089677B2 JP6089677B2 JP2012277231A JP2012277231A JP6089677B2 JP 6089677 B2 JP6089677 B2 JP 6089677B2 JP 2012277231 A JP2012277231 A JP 2012277231A JP 2012277231 A JP2012277231 A JP 2012277231A JP 6089677 B2 JP6089677 B2 JP 6089677B2
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0083—Converters characterised by their input or output configuration
- H02M1/0085—Partially controlled bridges
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
- Y02P80/00—Climate change mitigation technologies for sector-wide applications
- Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
- Dc-Dc Converters (AREA)
Description
本発明は、電源装置に関する。 The present invention relates to a power supply device.
近年、様々な分野におけるエネルギー資源の節約が注目され、例えば、電源の分野においてもその影響が波及している。具体的には、例えば、スイッチング電源装置のさらなる高効率化が求められるようになってきている。 In recent years, saving of energy resources in various fields has attracted attention, and for example, the influence has spread to the field of power supplies. Specifically, for example, higher efficiency of the switching power supply device has been demanded.
スイッチング電源装置の力率を改善するＰＦＣ（Power Factor Correction：力率改善）コンバータは、商用交流電源を入力して全波整流するダイオードブリッジと、その全波整流電圧を入力する昇圧チョッパー回路とで構成されている。さらに、ダイオードブリッジ回路での電力損失を低減するため、整流ブリッジ回路を設けないブリッジレスＰＦＣとして作用するスイッチング電源装置もある。 A power factor correction (PFC) converter that improves the power factor of a switching power supply unit is a diode bridge that performs full-wave rectification by inputting commercial AC power and a boost chopper circuit that inputs the full-wave rectified voltage. It is configured. Furthermore, there is a switching power supply device that acts as a bridgeless PFC without a rectifier bridge circuit in order to reduce power loss in the diode bridge circuit.
図１は、ブリッジレスＰＦＣ回路を有するスイッチング電源装置の回路図の一例を示す。図１に示すスイッチング電源装置において、第１の入力端子Ａ１と第２の入力端子Ａ２に商用交流電源が接続され、交流入力電圧ＶＡＣが入力される。このスイッチング電源装置の入力段には、交流入力電圧ＶＡＣを全波整流するダイオードブリッジが設けられていない。 FIG. 1 shows an example of a circuit diagram of a switching power supply device having a bridgeless PFC circuit. In the switching power supply device shown in FIG. 1, a commercial AC power supply is connected to the first input terminal A1 and the second input terminal A2, and the AC input voltage VAC is input. The input stage of this switching power supply device is not provided with a diode bridge for full-wave rectification of the AC input voltage VAC.
第１のスイッチング素子ＴＲ１と第１のダイオードＤ１を含む第１の直列回路が、二つの出力端子Ｐ１、Ｐ２に対して、並列接続されている。また、第２のスイッチング素子ＴＲ２と第２のダイオードＤ２を含む第２の直列回路が、二つの出力端子Ｐ１、Ｐ２に対して、並列接続されている。スイッチング素子には、例えば、ＭＯＳＦＥＴ（Metal Oxide Semiconductor Field Effect Transistor：金属酸化物半導体電界効果トランジスタ）が用いられる。 A first series circuit including a first switching element TR1 and a first diode D1 is connected in parallel to the two output terminals P1 and P2. A second series circuit including the second switching element TR2 and the second diode D2 is connected in parallel to the two output terminals P1 and P2. For example, a MOSFET (Metal Oxide Semiconductor Field Effect Transistor) is used as the switching element.
そして、二つの出力端子Ｐ１、Ｐ２に対して、ＤＣ出力を平滑するコンデンサＣ１による平滑回路が並列接続されている。 And the smoothing circuit by the capacitor | condenser C1 which smoothes DC output is parallelly connected with respect to the two output terminals P1 and P2.
Ｔ字型に接続された、第１のインダクタＬ１、第１のスイッチング素子ＴＲ１、第１のダイオードＤ１、及びコンデンサＣ１で第１のＰＦＣ回路を構成し、交流入力電圧ＶＡＣが正のサイクルの時に、交流入力電流に含まれる高調波等の歪みを低減し、電力の力率を改善するアクティブフィルタ回路として動作する。 The first inductor L1, the first switching element TR1, the first diode D1, and the capacitor C1 connected in a T shape form a first PFC circuit, and the AC input voltage VAC is in a positive cycle. It operates as an active filter circuit that reduces distortion such as harmonics contained in the AC input current and improves the power factor of power.
Ｔ字型に接続された、第２のインダクタＬ２、第２のスイッチング素子ＴＲ２、第２のダイオードＤ２、及びコンデンサＣ１で第２のＰＦＣ回路を構成し、交流入力電圧ＶＡＣが負のサイクルの時に、交流入力電流に含まれる高調波等の歪みを低減し、電力の力率を改善するアクティブフィルタ回路として動作する。 The second inductor L2, the second switching element TR2, the second diode D2, and the capacitor C1 connected in a T shape form a second PFC circuit, and the AC input voltage VAC is in a negative cycle. It operates as an active filter circuit that reduces distortion such as harmonics contained in the AC input current and improves the power factor of power.
第１のスイッチング素子ＴＲ１と第１のダイオードＤ１との接続点と交流入力電源の第１の入力端子Ａ１との間に第１のインダクタＬ１が挿入されている。また、第２のスイッチング素子ＴＲ２と第２のダイオードＤ２との接続点と交流入力電源の第２の入力端子Ａ２との間に第２のインダクタＬ２が挿入されている。 A first inductor L1 is inserted between a connection point between the first switching element TR1 and the first diode D1 and the first input terminal A1 of the AC input power supply. A second inductor L2 is inserted between the connection point of the second switching element TR2 and the second diode D2 and the second input terminal A2 of the AC input power supply.
第１の入力端子Ａ１と第１のインダクタＬ１との接続点と、出力端子Ｐ２のラインとの間に第１のリターンダイオードＤ３が挿入されている。第２の入力端子Ａ２と第２のインダクタＬ２との接続点と、出力端子Ｐ２のラインとの間に第２のリターンダイオードＤ４が挿入されている。 A first return diode D3 is inserted between the connection point between the first input terminal A1 and the first inductor L1 and the line of the output terminal P2. A second return diode D4 is inserted between the connection point of the second input terminal A2 and the second inductor L2 and the line of the output terminal P2.
図２は、交流入力電圧ＶＡＣが、正の半サイクルの時の図１に示したスイッチング電源装置の電流経路を示す図である。正の半サイクルにおいては、第１のスイッチング素子ＴＲ１をオフ・オンしてＰＦＣ制御を行なう。その際に、第２のスイッチング素子ＴＲ２も同時にオン・オフさせる。 FIG. 2 is a diagram illustrating a current path of the switching power supply device illustrated in FIG. 1 when the AC input voltage VAC is in a positive half cycle. In the positive half cycle, the first switching element TR1 is turned on / off to perform PFC control. At that time, the second switching element TR2 is also turned on / off simultaneously.
図２（Ａ）は、第１のスイッチング素子ＴＲ１がオンになった際の電流経路を示し、図２（Ｂ）は、第１のスイッチング素子ＴＲ１がオフになった際の電流経路を示す。 FIG. 2A shows a current path when the first switching element TR1 is turned on, and FIG. 2B shows a current path when the first switching element TR1 is turned off.
図２（Ａ）を参照して、第１のスイッチング素子ＴＲ１がオンの時は、第１の入力端子Ａ１から第１のインダクタＬ１に流れる電流は、第１のスイッチング素子ＴＲ１から、出力端子Ｐ２のラインに流れる。出力端子Ｐ２のラインに流れた電流は、リターンダイオードＤ４を介して第２の入力端子Ａ２に帰還するが、ＭＯＳＦＥＴである第２のスイッチング素子ＴＲ２もオンしているため、リターンダイオードＤ４での電圧降下よりも第２のスイッチング素子ＴＲ２の電圧降下の方が小さいので、帰還電流の大半は、第２のスイッチング素子ＴＲ２に流れ、リターンダイオードＤ４に流れる電流はわずかである。 Referring to FIG. 2A, when the first switching element TR1 is on, the current flowing from the first input terminal A1 to the first inductor L1 is output from the first switching element TR1 to the output terminal P2. Flowing in the line. The current flowing in the line of the output terminal P2 is fed back to the second input terminal A2 via the return diode D4. However, since the second switching element TR2 which is a MOSFET is also turned on, the voltage at the return diode D4 Since the voltage drop of the second switching element TR2 is smaller than the drop, most of the feedback current flows to the second switching element TR2, and the current flowing to the return diode D4 is small.
図２（Ｂ）を参照して、第１のスイッチング素子ＴＲ１がオフの時は、第１の入力端子Ａ１から第１のインダクタＬ１方向に流れる電流は、第１のスイッチング素子ＴＲ１を通らず、第１のダイオードＤ１を介して出力端子Ｐ１に流れる。出力端子Ｐ２からの帰還電流は、リターンダイオードＤ４を介して第２の入力端子Ａ２に帰還するが、第２のスイッチング素子ＴＲ２の寄生ダイオード（以降ボディダイオード）ＢＤ２と、第２のインダクタＬ２を介しても第２の入力端子Ａ２に帰還する。 Referring to FIG. 2B, when the first switching element TR1 is OFF, the current flowing from the first input terminal A1 toward the first inductor L1 does not pass through the first switching element TR1. It flows to the output terminal P1 through the first diode D1. The feedback current from the output terminal P2 is fed back to the second input terminal A2 via the return diode D4, but via the parasitic diode (hereinafter body diode) BD2 of the second switching element TR2 and the second inductor L2. However, it returns to the second input terminal A2.
インダクタには、電流を流し続ける性質があるため、第２のインダクタＬ２は、第１のスイッチング素子ＴＲ１がオンからオフになってもそのまま帰還電流を流し続ける。よって、第２のスイッチング素子ＴＲ２のボディダイオードＢＤ２にも帰還電流が流れ続ける。 Since the inductor has a property of continuously flowing a current, the second inductor L2 continues to flow a feedback current as it is even when the first switching element TR1 is turned off. Therefore, the feedback current continues to flow through the body diode BD2 of the second switching element TR2.
リターンダイオードＤ４には、第１のスイッチング素子ＴＲ１がオンからオフとなった瞬間に一旦電流が流れなくなり、それから徐々に流れだそうとするが、リターンダイオードＤ４の電圧降下よりもボディダイオードＢＤ２の電圧降下の方が小さいので、帰還電流の大半は、オフとなっている第２のスイッチング素子ＴＲ２のボディダイオードＢＤ２に流れ、リターンダイオードＤ４に流れる電流はわずかである。 In the return diode D4, the current once stops flowing at the moment when the first switching element TR1 is turned off, and then gradually flows, but the voltage of the body diode BD2 is more than the voltage drop of the return diode D4. Since the drop is smaller, most of the feedback current flows through the body diode BD2 of the second switching element TR2 that is off, and the current that flows through the return diode D4 is small.
帰還電流が、ボディダイオードＢＤ２を流れる間は、電力の損失が発生する。よって、スイッチング電源装置の出力効率をさらに向上させるためには、ボディダイオードＢＤ２に流れる帰還電流を減らす必要がある。 While the feedback current flows through the body diode BD2, power loss occurs. Therefore, in order to further improve the output efficiency of the switching power supply device, it is necessary to reduce the feedback current flowing through the body diode BD2.
ボディダイオードでの損失を減らすため、第１、及び第２のスイッチング素子ＴＲ１、ＴＲ２をボディダイオードの無いＧａＮ−ＨＥＭＴ（High Electron Mobility Transistor）にすることも考えられる。しかし、その場合、帰還電流は全てリターンダイオードに流れることになり、リターンダイオードで損失が起こる。リターンダイオードで損失は、ボディダイオードでの損失よりもさらに大きくなってしまう。 In order to reduce the loss in the body diode, the first and second switching elements TR1 and TR2 may be GaN-HEMT (High Electron Mobility Transistor) without a body diode. However, in that case, all the feedback current flows to the return diode, and loss occurs in the return diode. The loss in the return diode is even greater than the loss in the body diode.
本技術は、上記に鑑み、ブリッジレスＰＦＣのオフとなっているスイッチング素子のボディダイオードで損失される電力を低減することが可能な電源装置を提供することを目的とする。 In view of the above, an object of the present technology is to provide a power supply device capable of reducing the power lost in the body diode of the switching element in which the bridgeless PFC is turned off.
開示の電源装置によれば、第１の出力端子と第２の出力端子との間に接続され、第１のスイッチング素子と第１の整流素子とを含む第１の直列回路と、前記第１の出力端子と前記第２の出力端子との間に接続され、第２のスイッチング素子と第２の整流素子を含む第２の直列回路と、前記第１のスイッチング素子と前記第１の整流素子との接続点と交流入力の第１の入力端子との間に挿入された第１のインダクタと、前記第２のスイッチング素子と前記第２の整流素子との接続点と前記交流入力の第２の入力端子との間に挿入された第１のインダクタと、前記第１のインダクタと前記第１の入力端子との接続点と前記第２の出力端子との間に挿入された第３のスイッチング素子と、前記第２のインダクタと前記第２の入力端子との接続点と前記第２の出力端子との間に挿入された第４のスイッチング素子と、前記第１及び第２のスイッチング素子を制御する制御回路と、前記第３及び第４のスイッチング素子を制御する同期整流制御回路を有する電源装置が提供される。 According to the disclosed power supply apparatus, the first series circuit connected between the first output terminal and the second output terminal, the first series circuit including the first switching element and the first rectifying element, and the first A second series circuit including a second switching element and a second rectifying element, the first switching element and the first rectifying element connected between the output terminal and the second output terminal , A first inductor inserted between a connection point between the second switching element and the second rectifying element, and a second input terminal of the AC input. A first inductor inserted between the first input terminal and a third switching element inserted between the connection point between the first inductor and the first input terminal and the second output terminal. A connection point between the element, the second inductor, and the second input terminal; A fourth switching element inserted between the second output terminal, a control circuit for controlling the first and second switching elements, and a synchronous rectification control for controlling the third and fourth switching elements; A power supply having a circuit is provided.
開示の電源装置によれば、ブリッジレスＰＦＣ回路に、ＡＣ入力の正負のサイクルに合わせて帰還電流を流すスイッチを設けることで、オフとなっているスイッチング素子のボディダイオードに帰還電流が流れないようにして、ボディダイオードでの電力損失を減らし、電力効率を改善した電源装置を提供する。 According to the disclosed power supply apparatus, the bridgeless PFC circuit is provided with a switch that allows a feedback current to flow in accordance with the positive / negative cycle of the AC input, so that the feedback current does not flow through the body diode of the switching element that is turned off. Thus, it is possible to provide a power supply device that reduces power loss in the body diode and improves power efficiency.
最初に、図３を参照して、ボディダイオードでの損失を低減したブリッジレスＰＦＣ回路を有するスイッチング電源装置の比較例について説明する。 First, a comparative example of a switching power supply apparatus having a bridgeless PFC circuit with reduced loss in the body diode will be described with reference to FIG.
図３において、図１に示すスイッチング電源装置と同一又は同等の構成要素には同一符号を付し、その説明を省略する。 3, the same or equivalent components as those in the switching power supply device shown in FIG.
本比較例のスイッチング電源装置には、図１に示すスイッチング電源装置にあったリターンダイオードＤ３、Ｄ４に相当するものは無い。 The switching power supply of this comparative example does not correspond to the return diodes D3 and D4 in the switching power supply shown in FIG.
図３（Ａ）及び図３（Ｂ）は、交流入力電圧ＶＡＣが、正の半サイクルの時の電流経路を示す図である。正の半サイクルにおいては、第１のスイッチング素子ＴＲ１をスイッチングしてＰＦＣ制御を行ない、第２のスイッチング素子ＴＲ２は、オンのままとしている。 FIGS. 3A and 3B are diagrams showing current paths when the AC input voltage VAC is in the positive half cycle. In the positive half cycle, the PFC control is performed by switching the first switching element TR1, and the second switching element TR2 is kept on.
図３（Ａ）は、第１のスイッチング素子ＴＲ１がオンになった際の電流経路を示し、図３（Ｂ）は、第１のスイッチング素子ＴＲ１がオフになった際の電流経路を示す。 FIG. 3A shows a current path when the first switching element TR1 is turned on, and FIG. 3B shows a current path when the first switching element TR1 is turned off.
図３（Ａ）を参照して、第１のスイッチング素子ＴＲ１がオンの時は、第１の入力端子Ａ１から第１のインダクタＬ１に流れる電流は、第１のスイッチング素子ＴＲ１から、出力端子Ｐ２のラインに流れる。出力端子Ｐ２のラインに流れた電流は、オンとなっている第２のスイッチング素子ＴＲ２から第２の入力端子Ａ２に帰還する。 Referring to FIG. 3A, when the first switching element TR1 is on, the current flowing from the first input terminal A1 to the first inductor L1 is output from the first switching element TR1 to the output terminal P2. Flowing in the line. The current flowing in the line of the output terminal P2 returns to the second input terminal A2 from the second switching element TR2 that is turned on.
図３（Ｂ）を参照して、第１のスイッチング素子ＴＲ１がオフの時は、第１の入力端子Ａ１から第１のインダクタＬ１方向に流れる電流は、第１のスイッチング素子ＴＲ１を通らず、第１のダイオードＤ１を介して出力端子Ｐ１に流れる。出力端子Ｐ２からの帰還電流は、オンとなっている第２のスイッチング素子ＴＲ２から第２の入力端子Ａ２に帰還する。 Referring to FIG. 3B, when the first switching element TR1 is off, the current flowing from the first input terminal A1 toward the first inductor L1 does not pass through the first switching element TR1. It flows to the output terminal P1 through the first diode D1. The feedback current from the output terminal P2 returns from the second switching element TR2 that is turned on to the second input terminal A2.
本比較例のスイッチング電源装置においては、第２のスイッチング素子ＴＲ２をオンのままとすることで、リターンダイオードも要らなくなるし、ボディダイオードでの損失もなくなる。しかしながら、交流入力電圧ＶＡＣの半サイクルの間、第２のスイッチング素子ＴＲ２はオンしたままとなるため、この間にオン抵抗による電力の損失が発生する。 In the switching power supply device of this comparative example, by keeping the second switching element TR2 on, the return diode is not required and the loss in the body diode is also eliminated. However, since the second switching element TR2 remains on during the half cycle of the AC input voltage VAC, power loss due to the ON resistance occurs during this period.
スイッチング用トランジスタで電力が消費される原因は、トランジスタのオン抵抗と呼ばれるトランジスタがオンした状態でのソース・ドレイン間の抵抗成分によるもの、並びに、いわゆるスイッチングロスといわれるトランジスタのオン・オフの切り替え時の過渡状態で生じるものがある。 The cause of power consumption in the switching transistor is due to the resistance component between the source and drain when the transistor is turned on, which is called the transistor's on-resistance, and when the transistor is switched on / off, which is called switching loss. May occur in the transient state.
まず、トランジスタのオン抵抗に起因した問題は、トランジスタがオン状態の時に生じる。すなわち、トランジスタのオン抵抗は、トランジスタをオン状態にして、トランジスタに電流を流したとき、オームの法則によって、そのオン抵抗および電流によりトランジスタの電流の流れる端子間に電圧を発生させる。 First, a problem caused by the on-resistance of the transistor occurs when the transistor is on. That is, when the transistor is turned on and a current is passed through the transistor, the on-resistance of the transistor generates a voltage between the current-carrying terminals of the transistor by the on-resistance and the current according to Ohm's law.
ここで、トランジスタで消費される電力は、トランジスタに流れる電流と、トランジスタに電流が流れる両端子間に生じる電圧の積となるため、この電力は、スイッチング電源の出力として取り出せるものでは無く、トランジスタで熱に変換されて電力損失となる。 Here, the power consumed by the transistor is the product of the current flowing through the transistor and the voltage generated between both terminals through which the current flows, so this power cannot be extracted as the output of the switching power supply. It is converted into heat, resulting in power loss.
次に、スイッチングロスといわれるオン・オフの過渡状態で発生する損失は、オン・オフの切り替え時に、スイッチング時間と呼ばれる電流・電圧ともにゼロでない時間が存在するために発生する。過渡状態での電流・電圧の変化を近似的に時間の一関数であるとすると、スイッチングロスは、電流×電圧×スイッチング時間／２であらわすことができるため、スイッチング損失を減らすためには、トランジスタのドライブ能力を高く、つまりスイッチング速度を速くする必要がある。 Next, a loss that occurs in an on / off transient state, referred to as switching loss, occurs because there is a non-zero time for both current and voltage called switching time when switching on and off. If the change in current and voltage in a transient state is approximately a function of time, the switching loss can be expressed as current × voltage × switching time / 2. It is necessary to increase the drive capability of the system, that is, to increase the switching speed.
図４は、市販のシリコンＭＯＳＦＥＴのオン抵抗と出力容量によるスイッチングロスとの関係をプロットした図である。点線は、特定出力でのオン抵抗によるロスをあらわしている。図４より、オン抵抗の低いＭＯＳＦＥＴはスイッチングロスが大きく、スイッチングロスの低いＭＯＳＦＥＴは、オン抵抗が大きいことが解る。 FIG. 4 is a graph plotting the relationship between the on-resistance of a commercially available silicon MOSFET and the switching loss due to the output capacitance. The dotted line represents the loss due to the on-resistance at a specific output. From FIG. 4, it can be seen that a MOSFET having a low on-resistance has a large switching loss, and a MOSFET having a low switching loss has a large on-resistance.
ＰＦＣ制御は、１００ＫＨｚ〜２００ＫＨｚの比較的早い周期でスイッチングが行なわれるため、スイッチング素子には、スイッチングが早く、スイッチングロスの少ないＭＯＳＦＥＴを用いる方が望ましい。 In PFC control, switching is performed at a relatively fast cycle of 100 KHz to 200 KHz. Therefore, it is desirable to use a MOSFET that has a fast switching and a small switching loss as the switching element.
帰還電流を帰還するスイッチは、交流入力電圧ＶＡＣのサイクル（５０Ｈｚ〜６０Ｈｚ）の半分の期間、オンしたままとなるので、その期間に発生する熱に変換される損失を減らすため、オン抵抗の小さいＭＯＳＦＥＴを用いることが望ましい。 The switch that feeds back the feedback current remains on for a period of half of the cycle (50 Hz to 60 Hz) of the AC input voltage VAC, so that the on-resistance is small in order to reduce the loss that is converted into heat generated during that period. It is desirable to use a MOSFET.
しかしながら、図４から解る様に、スイッチングロスとオン抵抗の両方が小さいＭＯＳＦＥＴを選択するのは難しい。比較例のスイッチング電源装置においては、スイッチングロスとオン抵抗による損失のいずれが大きくなってしまうという問題がある。つまり、ＰＦＣ制御のためのスイッチングと電流リターンを同じスイッチング素子で行なうと電力損失が増えてしまうことになる。 However, as can be seen from FIG. 4, it is difficult to select a MOSFET having both a small switching loss and an on-resistance. In the switching power supply device of the comparative example, there is a problem that either the switching loss or the loss due to the on-resistance increases. That is, if the switching for PFC control and the current return are performed with the same switching element, the power loss increases.
以下に図面を参照して、本開示の技術にかかる好適な実施の形態を詳細に説明する。 Exemplary embodiments according to the technology of the present disclosure will be described below in detail with reference to the drawings.
図５は、開示の技術を適用した実施形態のスイッチング電源装置を示す回路図である。図５において、図１に示すスイッチング電源装置と同一又は同等の構成要素には同一符号を付し、その説明を省略する。 FIG. 5 is a circuit diagram illustrating a switching power supply apparatus according to an embodiment to which the disclosed technique is applied. In FIG. 5, the same or equivalent components as those in the switching power supply device shown in FIG.
本実施形態のスイッチング電源装置は、入力端子Ａ１、Ａ２、ＰＦＣ回路、ＰＦＣ制御回路５０、出力端子Ｐ１、Ｐ２、及び同期整流制御回路２０を含む。 The switching power supply device of the present embodiment includes input terminals A1 and A2, a PFC circuit, a PFC control circuit 50, output terminals P1 and P2, and a synchronous rectification control circuit 20.
交流電源１から入力端子Ａ１、Ａ２に、商用交流電力（８０〜２３０ＶＡＣ）が入力される。 Commercial AC power (80 to 230 VAC) is input from the AC power source 1 to the input terminals A1 and A2.
出力端子Ｐ１は、直流電力を出力する正極端子であり、出力端子Ｐ２は、直流電力を出力する負極端子である。 The output terminal P1 is a positive terminal that outputs DC power, and the output terminal P2 is a negative terminal that outputs DC power.
第１のスイッチング素子ＴＲ１と第１のダイオードＤ１を含む第１の直列回路が、二つの出力端子Ｐ１、Ｐ２に対して、並列接続されている。また、第２のスイッチング素子ＴＲ２と第２のダイオードＤ２を含む第２の直列回路が、二つの出力端子Ｐ１、Ｐ２に対して、並列接続されている。第１および第２のスイッチング素子には、例えば、スイッチング速度が早くて、スイッチングロスの少ないＭＯＳＦＥＴが望ましい。スイッチング速度が早く、高耐圧に耐えられる、窒素ガリウム（ＧａＮ）を用いたＧａＮ−ＨＥＭＴ（Gallium Nitride - High Electron Mobility Transistor：窒化ガリウム高電子移動度トランジスタ）とすることも可能である。 A first series circuit including a first switching element TR1 and a first diode D1 is connected in parallel to the two output terminals P1 and P2. A second series circuit including the second switching element TR2 and the second diode D2 is connected in parallel to the two output terminals P1 and P2. For the first and second switching elements, for example, MOSFETs with high switching speed and low switching loss are desirable. A GaN-HEMT (gallium nitride-high electron mobility transistor) using gallium nitrogen (GaN) that has a high switching speed and can withstand a high breakdown voltage can also be used.
第１のスイッチング素子ＴＲ１と第１のダイオードＤ１との接続点と入力端子Ａ１との間に第１のインダクタＬ１が挿入されている。また、第２のスイッチング素子ＴＲ２と第２のダイオードＤ２との接続点と入力端子Ａ２との間に第２のインダクタＬ２が挿入されている。第１及び第２のインダクタＬ１、Ｌ２には、例えば、昇圧用のインダクタが用いられる。 A first inductor L1 is inserted between a connection point between the first switching element TR1 and the first diode D1 and the input terminal A1. A second inductor L2 is inserted between the connection point between the second switching element TR2 and the second diode D2 and the input terminal A2. For example, boosting inductors are used as the first and second inductors L1 and L2.
そして、二つの出力端子Ｐ１、Ｐ２に対して、ＤＣ出力を平滑する平滑コンデンサＣ１が並列接続されている。 A smoothing capacitor C1 that smoothes the DC output is connected in parallel to the two output terminals P1 and P2.
Ｔ字型に接続された、第１のインダクタＬ１、第１のスイッチング素子ＴＲ１、第１のダイオードＤ１、及び平滑コンデンサＣ１で第１のＰＦＣ回路を構成する。Ｔ字型に接続された、第２のインダクタＬ２、第２のスイッチング素子ＴＲ２、第２のダイオードＤ２、及び平滑コンデンサＣ１で第２のＰＦＣ回路を構成する。 A first PFC circuit is configured by the first inductor L1, the first switching element TR1, the first diode D1, and the smoothing capacitor C1 connected in a T-shape. The second inductor L2, the second switching element TR2, the second diode D2, and the smoothing capacitor C1 connected in a T shape form a second PFC circuit.
第１のスイッチング素子ＴＲ１及び第２のスイッチング素子ＴＲ２は、ＰＦＣ制御回路５０からゲートにパルス状のゲート電圧が印加されることによってオフ・オン動作が行われ、ＰＷＭ（Pulse Width Modulation：パルス幅変調）駆動される。 The first switching element TR1 and the second switching element TR2 are turned on and off by applying a pulsed gate voltage from the PFC control circuit 50 to the gate, and PWM (Pulse Width Modulation) ) Driven.
ＰＦＣ制御回路５０は、第１及び第２のスイッチング素子ＴＲ１、ＴＲ２のゲートに印加するパルス状のゲート電圧を出力する。ＰＦＣ制御回路５０は、入力端子Ａ１、Ａ２から入力されるＡＣ電力の電圧値、第１及び第２のスイッチング素子ＴＲ１、ＴＲ２に流れる電流の電流値、平滑コンデンサＣ１の出力側の電圧値に基づいてゲート電圧のデューティ比を決定し、第１及び第２のスイッチング素子ＴＲ１、ＴＲ２のゲートに印加する。ＰＦＣ制御回路５０としては、例えば、第１及び第２のスイッチング素子ＴＲ１、ＴＲ２に流れる電流値、ＤＣ出力電圧値、ＡＣ入力電圧値に基づいてデューティ比を演算できるマルチプライヤ回路を用いればよい。 The PFC control circuit 50 outputs a pulsed gate voltage applied to the gates of the first and second switching elements TR1 and TR2. The PFC control circuit 50 is based on the voltage value of the AC power input from the input terminals A1 and A2, the current value of the current flowing through the first and second switching elements TR1 and TR2, and the voltage value on the output side of the smoothing capacitor C1. Thus, the duty ratio of the gate voltage is determined and applied to the gates of the first and second switching elements TR1 and TR2. As the PFC control circuit 50, for example, a multiplier circuit that can calculate a duty ratio based on a current value flowing through the first and second switching elements TR1 and TR2, a DC output voltage value, and an AC input voltage value may be used.
第１のＰＦＣ回路は、交流入力電圧ＶＡＣが正のサイクルの時に、交流入力電流に含まれる高調波等の歪みを低減し、電力の力率を改善するアクティブフィルタ回路として動作する。第２のＰＦＣ回路は、交流入力電圧ＶＡＣが負のサイクルの時に、交流入力電流に含まれる高調波等の歪みを低減し、電力の力率を改善するアクティブフィルタ回路として動作する。 The first PFC circuit operates as an active filter circuit that reduces distortion such as harmonics included in the AC input current and improves the power factor of the power when the AC input voltage VAC is in a positive cycle. The second PFC circuit operates as an active filter circuit that reduces distortion such as harmonics included in the AC input current and improves the power factor of the power when the AC input voltage VAC is in a negative cycle.
第１及び第２のダイオードＤ１、Ｄ２は、第１及び第２のインダクタＬ１、Ｌ２から平滑コンデンサＣ１の方向の整流方向を有していればよく、例えば、ファーストリカバリーダイオード、ＳｉＣショットキーダイオードが用いられる。 The first and second diodes D1 and D2 only have to have a rectification direction from the first and second inductors L1 and L2 to the smoothing capacitor C1. For example, a fast recovery diode or a SiC Schottky diode may be used. Used.
入力端子Ａ１と第１のインダクタＬ１との接続点と、出力端子Ｐ２のラインとの間に第１の同期整流スイッチＳＷ１が挿入されている。入力端子Ａ２と第２のインダクタＬ２との接続点と、出力端子Ｐ２のラインとの間に第２の同期整流スイッチＳＷ２が挿入されている。第１および第２の同期整流スイッチＳＷ１、ＳＷ２には、例えば、オン抵抗の小さいＭＯＳＦＥＴが望ましい。あるいは、オン抵抗の小さいＧａＮ−ＨＥＭＴとすることも可能である。 A first synchronous rectification switch SW1 is inserted between the connection point between the input terminal A1 and the first inductor L1 and the line of the output terminal P2. A second synchronous rectification switch SW2 is inserted between the connection point between the input terminal A2 and the second inductor L2 and the line of the output terminal P2. For the first and second synchronous rectification switches SW1 and SW2, for example, MOSFETs with low on-resistance are desirable. Alternatively, a GaN-HEMT with a low on-resistance can be used.
第１および第２の同期整流スイッチＳＷ１、ＳＷ２のオン・オフは、同期整流駆動回路２２によって制御される。第１および第２の同期整流スイッチＳＷ１、ＳＷ２及び同期整流駆動回路２２で、同期整流制御回路２０を構成する。 The on / off of the first and second synchronous rectification switches SW 1 and SW 2 is controlled by the synchronous rectification drive circuit 22. The first and second synchronous rectification switches SW1 and SW2 and the synchronous rectification drive circuit 22 constitute a synchronous rectification control circuit 20.
次に、図６を用いて、本実施形態のスイッチング電源装置の動作について説明する。 Next, the operation of the switching power supply device of this embodiment will be described with reference to FIG.
図６は、交流入力電圧ＶＡＣが、正の半サイクルの時の図５に示したスイッチング電源装置の電流経路を示す図である。正の半サイクルにおいては、第１のスイッチング素子ＴＲ１をオフ・オンしてＰＦＣ制御する。その際に、第２のスイッチング素子ＴＲ２は、オフのままとする。 FIG. 6 is a diagram showing a current path of the switching power supply device shown in FIG. 5 when the AC input voltage VAC is in the positive half cycle. In the positive half cycle, the first switching element TR1 is turned on / off to perform PFC control. At that time, the second switching element TR2 remains off.
図６（Ａ）は、第１のスイッチング素子ＴＲ１がオンになった際の電流経路を示し、
図６（Ｂ）は、第１のスイッチング素子ＴＲ１がオフになった際の電流経路を示す。
FIG. 6A shows a current path when the first switching element TR1 is turned on.
FIG. 6B shows a current path when the first switching element TR1 is turned off.
図６（Ａ）を参照して、第１のスイッチング素子ＴＲ１がオンの時は、入力端子Ａ１から第１のインダクタＬ１に流れる電流は、第１のスイッチング素子ＴＲ１から、出力端子Ｐ２のラインに流れる。同期整流駆動回路２２は、交流入力電圧ＶＡＣが、正のサイクルにあることを検出して、第２の同期整流スイッチＳＷ２のオンにする。 Referring to FIG. 6A, when the first switching element TR1 is on, the current flowing from the input terminal A1 to the first inductor L1 flows from the first switching element TR1 to the line of the output terminal P2. Flowing. The synchronous rectification drive circuit 22 detects that the AC input voltage VAC is in a positive cycle, and turns on the second synchronous rectification switch SW2.
出力端子Ｐ２のラインに流れた電流は、第２の同期整流スイッチＳＷ２を介して、第２の入力端子Ａ２に帰還する。第２の同期整流スイッチＳＷ２での電圧降下は、第２のスイッチング素子ＴＲ２のボディダイオードＢＤ２の電圧降下に比べてはるかに小さいので、帰還電流は、ボディダイオードＢＤ２には流れず、第２の同期整流スイッチＳＷ２に流れる。 The current flowing through the line of the output terminal P2 is fed back to the second input terminal A2 via the second synchronous rectification switch SW2. Since the voltage drop at the second synchronous rectification switch SW2 is much smaller than the voltage drop of the body diode BD2 of the second switching element TR2, the feedback current does not flow to the body diode BD2, and the second synchronization It flows to the rectifying switch SW2.
図６（Ｂ）を参照して、第１のスイッチング素子ＴＲ１がオフの時は、入力端子Ａ１から第１のインダクタＬ１方向に流れる電流は、第１のスイッチング素子ＴＲ１を通らず、第１のダイオードＤ１を介して出力端子Ｐ１に流れる。出力端子Ｐ２からの帰還電流は、第２の同期整流スイッチＳＷ２を介して、第２の入力端子Ａ２に帰還する。第２の同期整流スイッチＳＷ２での電圧降下は、第２のスイッチング素子ＴＲ２のボディダイオードＢＤ２の電圧降下に比べてはるかに小さいので、帰還電流は、ボディダイオードＢＤ２には流れず、第２の同期整流スイッチＳＷ２に流れる。 Referring to FIG. 6B, when the first switching element TR1 is OFF, the current flowing from the input terminal A1 toward the first inductor L1 does not pass through the first switching element TR1 and the first switching element TR1. It flows to the output terminal P1 through the diode D1. The feedback current from the output terminal P2 is fed back to the second input terminal A2 via the second synchronous rectification switch SW2. Since the voltage drop at the second synchronous rectification switch SW2 is much smaller than the voltage drop of the body diode BD2 of the second switching element TR2, the feedback current does not flow to the body diode BD2, and the second synchronization It flows to the rectifying switch SW2.
第２の同期整流スイッチＳＷ２がオンとなっている期間は、交流入力電圧ＶＡＣのサイクル（５０Ｈｚ〜６０Ｈｚ）の半分の期間である。第２の同期整流スイッチＳＷ２を、オン抵抗の小さいＭＯＳＦＥＴとしておけば、第２の同期整流スイッチＳＷ２がオンとなっている期間に熱に変換される損失を小さくすることができる。 The period during which the second synchronous rectification switch SW2 is on is a half period of the cycle (50 Hz to 60 Hz) of the AC input voltage VAC. If the second synchronous rectification switch SW2 is a MOSFET having a low on-resistance, the loss converted into heat during the period when the second synchronous rectification switch SW2 is on can be reduced.
本実施形態によれば、オフとなっているスイッチング素子のボディダイオードに帰還電流が流れないので、ボディダイオードでの電力の損失がなく、また、同期整流スイッチでのオン抵抗による損失も小さくできるので、電力効率の良いスイッチング電源装置を提供することが可能となる。 According to the present embodiment, since no feedback current flows through the body diode of the switching element that is turned off, there is no power loss in the body diode, and loss due to the on-resistance in the synchronous rectifier switch can be reduced. Thus, it is possible to provide a switching power supply device with good power efficiency.
次に、図７、図８を用いて、本実施形態の同期整流駆動回路２２の一例について説明する。 Next, an example of the synchronous rectification drive circuit 22 according to the present embodiment will be described with reference to FIGS.
図７は、第１及び第２の同期整流スイッチＳＷ１、ＳＷ２のゲートを交流入力電圧ＶＡＣ同期にさせて駆動するための同期整流駆動回路２２の回路例である。本実施例では、同期整流スイッチＳＷ１、ＳＷ２のゲートバイアスは、交流入力電圧ＶＡＣを抵抗分割することによって作成している。 FIG. 7 is a circuit example of the synchronous rectification drive circuit 22 for driving the gates of the first and second synchronous rectification switches SW1 and SW2 in synchronization with the AC input voltage VAC. In this embodiment, the gate biases of the synchronous rectification switches SW1 and SW2 are created by dividing the AC input voltage VAC by resistance.
交流入力電圧のワールドワイド（８０〜２３０ＶＡＣ）電圧に対応するため、分割抵抗Ｒ１：Ｒ２、Ｒ４：Ｒ３の抵抗比をたとえば２：１とし、チェナーダイオードＤ１〜Ｄ４により最大電圧を制限している。 In order to correspond to the world wide (80 to 230 VAC) voltage of the AC input voltage, the resistance ratio of the dividing resistors R1: R2 and R4: R3 is set to 2: 1, for example, and the maximum voltage is limited by the Zener diodes D1 to D4. .
図８は、図７に示す同期整流駆動回路２２に、交流入力電圧にＡＣ２３０Ｖを入力した場合のシミュレーション波形を示す。図８（Ａ）は、交流入力電圧波形、図８（Ｂ）は第１の同期整流スイッチＳＷ１のゲート波形、図８（Ｃ）は第２の同期整流スイッチＳＷ２のゲート波形、図８（Ｄ）はスイッチングロス、図８（Ｅ）はＤＣ出力電圧波形を示す。 FIG. 8 shows simulation waveforms when AC 230 V is input as the AC input voltage to the synchronous rectification drive circuit 22 shown in FIG. 8A shows an AC input voltage waveform, FIG. 8B shows a gate waveform of the first synchronous rectification switch SW1, FIG. 8C shows a gate waveform of the second synchronous rectification switch SW2, and FIG. ) Shows a switching loss, and FIG. 8E shows a DC output voltage waveform.
図８（Ｂ）、図８（Ｃ）から、交流入力電圧ＶＡＣに対応して第１及び第２の同期整流スイッチＳＷ１、ＳＷ２のゲートにバイアスが加えられていることが分かる。本実施例では、抵抗分圧回路によってゲートバイアスを作成したが、専用の補助電源と制御回路を使用しても同様の動作が可能である。 From FIG. 8B and FIG. 8C, it can be seen that a bias is applied to the gates of the first and second synchronous rectification switches SW1 and SW2 corresponding to the AC input voltage VAC. In this embodiment, the gate bias is created by the resistance voltage dividing circuit, but the same operation is possible even if a dedicated auxiliary power source and a control circuit are used.
図９は、同期整流駆動回路の別の実施例の同期整流駆動回路２４の回路例である。図１０は、図９に示す同期整流駆動回路２４に、交流入力電圧にＡＣ２３０Ｖを入力した場合のシミュレーション波形を示す。 FIG. 9 is a circuit example of the synchronous rectification drive circuit 24 of another embodiment of the synchronous rectification drive circuit. FIG. 10 shows simulation waveforms when AC 230 V is input as the AC input voltage to the synchronous rectification drive circuit 24 shown in FIG.
図７に示す同期整流駆動回路２２では、同期整流スイッチＳＷ１、ＳＷ２にオン抵抗が１００ｍΩ以下であるようなＭＯＳＦＥＴを用いることを想定しているが、さらにオン抵抗の低いＭＯＳＦＥＴを用いる場合、低電圧入力時にオン、オフが遅くなって同期整流スイッチＳＷ１と、同期整流スイッチＳＷ２の両方が同時にオンしてしまい貫通電流が発生して、スイッチングロスの増大やのＭＯＳＦＥＴ故障につながる場合がある。 In the synchronous rectification drive circuit 22 shown in FIG. 7, it is assumed that MOSFETs having an on-resistance of 100 mΩ or less are used for the synchronous rectification switches SW1 and SW2. When input is turned on and off, the synchronous rectification switch SW1 and the synchronous rectification switch SW2 are both turned on at the same time, and a through current may be generated, leading to an increase in switching loss and a MOSFET failure.
図９に示す同期整流駆動回路２４では、同期整流スイッチＳＷ１と、同期整流スイッチＳＷ２のゲート前に追加したトランジスタＱ１、Ｑ２により、同期整流スイッチＳＷ１、ＳＷ２のオフ時にゲートの電荷を引き抜くことにより貫通電流の発生を防止することができる。 In the synchronous rectification drive circuit 24 shown in FIG. 9, the synchronous rectification switch SW1 and the transistors Q1 and Q2 added before the gate of the synchronous rectification switch SW2 are used to pull out the gate charge when the synchronous rectification switches SW1 and SW2 are turned off. Generation of current can be prevented.
以上本発明の好ましい実施形態について詳述したが、本発明は係る特定の実施形態に限定されるものではなく、特許請求の範囲に記載された本発明の要旨の範囲内において、種々の変形・変更が可能である。 Although the preferred embodiments of the present invention have been described in detail above, the present invention is not limited to the specific embodiments, and various modifications and changes can be made within the scope of the gist of the present invention described in the claims. It can be changed.
１ 交流電源
２０ 同期整流制御回路
２２、２４ 同期整流駆動回路
５０ ＰＦＣ制御回路
Ａ１、Ａ２ 入力端子
Ｃ１ コンデンサ、平滑コンデンサ
Ｐ１、Ｐ２ 出力端子
Ｄ１、Ｄ２ ダイオード
Ｄ３、Ｄ４ リターンダイオード
Ｌ１、Ｌ２ インダクタ
ＴＲ１、ＴＲ２ スイッチング素子
ＢＤ１、ＢＤ２ ボディダイオード
ＳＷ１、ＳＷ２ 同期整流スイッチ
DESCRIPTION OF SYMBOLS 1 AC power supply 20 Synchronous rectification control circuit 22, 24 Synchronous rectification drive circuit 50 PFC control circuit A1, A2 Input terminal C1 Capacitor, smoothing capacitor P1, P2 Output terminal D1, D2 Diode D3, D4 Return diode L1, L2 Inductor TR1, TR2 Switching element BD1, BD2 Body diode SW1, SW2 Synchronous rectification switch
Claims (7)
前記第１の出力端子と前記第２の出力端子との間に接続され、第２のスイッチング素子と第２の整流素子を含む第２の直列回路と、
前記第１のスイッチング素子と前記第１の整流素子との接続点と交流入力の第１の入力端子との間に挿入された第１のインダクタと、
前記第２のスイッチング素子と前記第２の整流素子との接続点と前記交流入力の第２の入力端子との間に挿入された第２のインダクタと、
前記第１のインダクタと前記第１の入力端子との接続点と前記第２の出力端子との間に挿入された第３のスイッチング素子と、
前記第２のインダクタと前記第２の入力端子との接続点と前記第２の出力端子との間に挿入された第４のスイッチング素子と、
前記第１及び第２スイッチング素子を制御する制御回路と、
前記第３及び第４のスイッチング素子を制御する同期整流制御回路と
を含み、
前記第３及び第４のスイッチング素子は、前記第１及び第２のスイッチング素子よりもオン抵抗の小さい
ことを特徴とする電源装置。 A first series circuit connected between the first output terminal and the second output terminal and including a first switching element and a first rectifying element;
A second series circuit connected between the first output terminal and the second output terminal and including a second switching element and a second rectifying element;
A first inductor inserted between a connection point between the first switching element and the first rectifying element and a first input terminal of an AC input;
A second inductor inserted between a connection point between the second switching element and the second rectifying element and a second input terminal of the AC input;
A third switching element inserted between a connection point between the first inductor and the first input terminal and the second output terminal;
A fourth switching element inserted between a connection point between the second inductor and the second input terminal and the second output terminal;
A control circuit for controlling the first and second switching elements;
A synchronous rectification control circuit for controlling the third and fourth switching elements ,
The power supply apparatus according to claim 3, wherein the third and fourth switching elements have lower on-resistance than the first and second switching elements .
前記交流入力電圧が正の場合、前記第３のスイッチング素子をオフするとともに、第４のスイッチング素子をオンし、
前記交流入力電圧が負の場合、前記第３のスイッチング素子をオンするとともに、第４のスイッチング素子をオフする
ことを特徴とする請求項１に記載の電源装置。 The synchronous rectification control circuit includes:
When the AC input voltage is positive , the third switching element is turned off and the fourth switching element is turned on.
2. The power supply device according to claim 1, wherein when the AC input voltage is negative, the third switching element is turned on and the fourth switching element is turned off.
ことを特徴とする請求項１に記載の電源装置。 The power supply apparatus according to claim 1, wherein the first and second switching elements are field effect transistors.
ことを特徴とする請求項３に記載の電源装置。 The power supply apparatus according to claim 3, wherein the third and fourth switching elements are field effect transistors.
ことを特徴とする請求項１に記載の電源装置。 The power supply apparatus according to claim 1, wherein the first and second switching elements are faster in switching speed than the third and fourth switching elements .
ことを特徴とする請求項１に記載の電源装置。 The power supply apparatus according to claim 1, wherein the first and second switching elements are gallium nitride high electron mobility transistors .
ことを特徴とする請求項１に記載の電源装置。
The power supply apparatus according to claim 1, wherein the third and fourth switching elements are gallium nitride high electron mobility transistors .
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| JP2012277231A JP6089677B2 (en) | 2012-12-19 | 2012-12-19 | Power supply |
| US14/065,799 US8749210B1 (en) | 2012-12-19 | 2013-10-29 | Power supply device |
| TW102139535A TWI559661B (en) | 2012-12-19 | 2013-10-31 | Power supply device |
| KR1020130139881A KR101580721B1 (en) | 2012-12-19 | 2013-11-18 | Power supply device |
| DE102013223457.0A DE102013223457A1 (en) | 2012-12-19 | 2013-11-18 | Power supply apparatus |
| CN201310594116.8A CN103888000B (en) | 2012-12-19 | 2013-11-21 | Power supply device |
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| JP7010015B2 (en) * | 2018-01-18 | 2022-01-26 | Tdk株式会社 | Power supply |
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| CN108448888B (en) * | 2018-04-10 | 2019-07-16 | 上海推拓科技有限公司 | Switching power circuit |
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| CN112152452B (en) * | 2019-06-26 | 2022-02-08 | 台达电子工业股份有限公司 | Power supply circuit and operation method |
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