JP5989058B2 - Delay adjustment method for semiconductor device and DLL circuit - Google Patents

Description

  The present invention relates to a clock control circuit and a semiconductor device including the same, and more particularly to a clock control circuit that adjusts the phase and duty of a clock signal, such as a DLL circuit and a duty correction circuit, and a semiconductor device including the same.

  In recent years, a synchronous memory that performs an operation synchronized with a clock is widely used as a main memory of a personal computer or the like. In particular, in a DDR (Double Data Rate) type synchronous memory, since input / output data must be accurately synchronized with an external clock signal, a DLL for generating an internal clock signal synchronized with the external clock signal is required. A circuit is essential (see Patent Document 1).

  The DLL circuit includes a counter circuit whose count value is updated based on the phase of the external clock signal, and a delay line that generates an internal clock signal by delaying the external clock signal based on the count value of the counter circuit. Yes. The count value is updated at a predetermined sampling period. Therefore, when the phase determination result is temporarily reversed due to the influence of noise or the like at the timing of updating the count value, the count value is updated in the direction opposite to the original update direction. That is, there is a case where the delay amount of the delay line should be increased but decreased, and conversely, the delay amount should be decreased.

  In addition, a jitter component may be superimposed on the external clock signal. The jitter component is a fluctuation of the clock frequency, and this fluctuation has a predetermined frequency. When the jitter component affects the DLL circuit, in some cases, even when the phase is greatly shifted, a loop in which up-counting and down-counting are alternately repeated is entered, and the state cannot be escaped.

  On the other hand, the period for locking the DLL circuit is determined by the standard. For this reason, if the delay line is adjusted in the reverse direction due to the influence of noise or enters the loop due to the influence of jitter components, the DLL circuit cannot be locked within the period defined by the standard.

JP 2008-217947 A

  As described above, the conventional DLL circuit has a problem that it cannot be locked correctly when it is affected by noise and jitter components. Such a problem is not limited to the DLL circuit, but also occurs in other types of clock control circuits that control the clock signal, such as a duty correction circuit that corrects the duty of the internal clock signal. In other words, even in the duty correction circuit, the internal clock signal may not be adjusted to a desired duty when affected by noise and jitter components.

  A clock control circuit according to an aspect of the present invention includes a phase determination circuit that generates a phase determination signal based on a phase of a first clock signal, and a count value is updated for each sampling period based on the phase determination signal. A delay circuit for generating a second clock signal by delaying the first clock signal based on the count value, and a response to the fact that the phase determination signal indicates one of the logic levels. And an invalidation circuit that invalidates subsequent changes in the phase determination signal within the same sampling period.

  A semiconductor device according to the present invention has substantially the same circuit configuration as the clock control circuit, an output buffer that outputs an external output signal in synchronization with the second clock signal, and an output buffer. A replica buffer that outputs a third clock signal in synchronization with the second clock signal, and the phase determination circuit determines the phase of the first clock signal by comparing the first and third clock signals It is characterized by doing.

  A clock control circuit according to another aspect of the present invention includes a delay line that generates a second clock signal by delaying the first clock signal, and a duty determination signal based on the duty of the second clock signal. A duty determination circuit for generating a delay circuit, a counter circuit in which a count value indicating a delay amount of the delay line is updated for each sampling period based on the duty determination signal, and the duty determination signal indicates one logic level In response to this, it comprises a nullifying circuit that nullifies subsequent changes in the duty determination signal within the same sampling period.

  As described above, according to the present invention, when the determination signal changes within the sampling period, the determination signal is fixed to a predetermined logic level by the invalidation circuit. It is possible to eliminate a component that affects the determination signal. Therefore, if the clock control circuit according to the present invention is applied to a DLL circuit, the phenomenon that the DLL circuit does not lock for a long time can be prevented. Further, when the clock control circuit according to the present invention is applied to the duty correction circuit, it is possible to prevent a phenomenon that the internal clock signal cannot be adjusted to a desired duty for a long time.

1 is a block diagram showing a configuration of a semiconductor device 10 according to a preferred first embodiment of the present invention. 3 is a circuit diagram of an invalidation circuit 200. FIG. 3 is a timing chart showing the operation of the DLL circuit according to the first embodiment. It is a circuit diagram of the invalidation circuit 200a used in 2nd Embodiment. 6 is a timing chart showing the operation of the DLL circuit according to the second embodiment. It is a block diagram which shows the structure of the semiconductor device 30 by preferable 3rd Embodiment of this invention. It is a block diagram which shows the structure of the semiconductor device 40 by preferable 4th Embodiment of this invention. It is a block diagram which shows the structure of the semiconductor device 50 by preferable 5th Embodiment of this invention. It is a block diagram which shows the structure of the semiconductor device 60 by preferable 6th Embodiment of this invention.

  Hereinafter, preferred embodiments of the present invention will be described in detail with reference to the accompanying drawings.

  FIG. 1 is a block diagram showing a configuration of a semiconductor device 10 according to a preferred first embodiment of the present invention.

  As shown in FIG. 1, the semiconductor device 10 according to the present embodiment includes an internal circuit 11 that outputs an internal output signal DR, an output buffer 12 that outputs an external output signal DQ based on the internal output signal DR, and an output buffer 12. A DLL circuit 100 for controlling the operation timing of the. The internal circuit 11 differs depending on the type of the semiconductor device 10. For example, if the semiconductor device 10 according to the present embodiment is a DRAM, a memory cell array, a column switch, a read amplifier, and the like are included.

  The output buffer 12 is a circuit that outputs the external output signal DQ to the outside via the output terminal 13, and the output timing of the external output signal DQ is the external clock signal CLK (first output) that is input via the clock terminal 14. Clock signal). The operation timing of the output buffer 12 is controlled by the DLL circuit 100. Hereinafter, the configuration of the DLL circuit 100 will be described in detail.

  As shown in FIG. 1, the DLL circuit 100 includes a delay line 110, a frequency dividing circuit 120, a counter circuit 130, a phase determination circuit 140, and an invalidation circuit 200.

  The delay line 110 is a circuit that generates the internal clock signal LCLK (second clock signal) by delaying the external clock signal CLK. Although not particularly limited, the delay line 110 includes a coarse delay line that delays the external clock signal with a relatively coarse adjustment pitch, and a fine delay line that delays the external clock signal with a relatively fine adjustment pitch. It is preferable to include.

  As shown in FIG. 1, the internal clock signal LCLK is supplied to the output buffer 12 and the replica buffer 15. As described above, the output buffer 12 is a circuit that receives the internal output signal DR supplied from the internal circuit 11 and supplies it to the output terminal 13 as the external output signal DQ. On the other hand, the replica buffer 15 has substantially the same circuit configuration as the output buffer 12, and is a circuit that outputs a replica clock signal RCLK (third clock signal) in synchronization with the internal clock signal LCLK. As a result, the phase of the replica clock signal RCLK exactly matches the phase of the external output signal DQ. However, the size of the transistor constituting the replica buffer 15 does not have to be the same as the size of the transistor constituting the output buffer 12, and a shrunken transistor may be used as long as the impedance is substantially the same. .

  The frequency dividing circuit 120 is a circuit that generates a reset signal RST that is a one-shot pulse by dividing the external clock signal CLK. The reset signal RST is supplied to the invalidation circuit 200 and also supplied to the delay circuit 150. The delay circuit 150 is a circuit that generates the update timing signal SYNCLK by delaying the reset signal RST. The update timing signal SYNCLK is supplied to the counter circuit 130 and is used as a synchronization signal indicating the timing at which the count value of the counter circuit 130 is updated. Therefore, the activation cycle of the update timing signal SYNCLK is defined as the sampling cycle of the DLL circuit 100. Note that the delay amount of the delay circuit 150 is preferably slightly shorter than the sampling period.

  Here, the reason why the frequency dividing circuit 120 is used to generate the reset signal RST is that a certain period of time is required for updating the counter circuit 130 and changing the delay amount of the delay line 110, and the external clock signal CLK This is because it is difficult to update the counter circuit 130 and change the delay amount of the delay line 110 every period. In addition, if the counter circuit 130 is updated and the delay amount of the delay line 110 is changed more frequently than necessary, the power consumption is significantly increased.

  The counter circuit 130 is a circuit for setting the delay amount of the delay line 110, and its count value is updated in synchronization with the update timing signal SYNCLK. The increase / decrease of the count value is determined based on the phase determination signal PD1 supplied from the invalidation circuit 200. That is, when the phase determination signal PD1 indicates an up count (when it is at a high level), the counter circuit 130 counts up the count value in synchronization with the update timing signal SYNCLK. Increase the amount. Conversely, when the phase determination signal PD1 indicates a down count (when it is at a low level), the counter circuit 130 counts down the count value in synchronization with the update timing signal SYNCLK. Reduce the amount of delay.

  The phase determination circuit 140 is a circuit that detects a phase difference between the external clock signal CLK and the replica clock signal RCLK. As described above, the phase of the replica clock signal RCLK is adjusted by the delay line 110 so as to match the phase of the external output signal DQ. However, the variation in parameters that affect the delay amount of the delay line 110 such as voltage and temperature, The phase of the external clock signal CLK itself changes every moment due to the frequency variation of the external clock signal CLK itself. The phase determination circuit 140 detects such a change and determines whether the replica clock signal RCLK is advanced or delayed with respect to the external clock signal CLK. The determination is performed every cycle of the external clock signal CLK, and the result is supplied to the invalidation circuit 200 as the phase determination signal PD0.

  The invalidation circuit 200 is a circuit that receives the phase determination signal PD0 and the reset signal RST and generates the phase determination signal PD1 based on them.

  FIG. 2 is a circuit diagram of the invalidation circuit 200.

  As shown in FIG. 2, the invalidation circuit 200 inverts the reset signal RST and supplies it to the reset input terminal (R) of the SR latch circuit 210 and the SR latch circuit 210 including the NAND circuits 201 and 202 connected in circulation. And an inverter 204 that inverts the phase determination signal PD0 and supplies the inverted signal to the set input terminal (S) of the SR latch circuit 210.

  With this configuration, when the phase determination signal PD0 becomes high level, the SR latch circuit 210 is set regardless of the logic level of the reset signal RST, and the phase determination signal PD1 that is the output becomes high level. Here, the phase determination signal PD0 becomes high level when the phase determination circuit 140 detects that the phase of the replica clock signal RCLK is ahead of the external clock signal CLK. That is, the delay amount of the delay line 110 needs to be increased.

  On the other hand, when the reset signal RST is at a high level and the phase determination signal PD0 is at a low level, the SR latch circuit 210 is in a reset state, and the output of the phase determination signal PD1 is at a low level. Here, the phase determination signal PD0 becomes low level when the phase determination circuit 140 detects that the phase of the replica clock signal RCLK is delayed from the external clock signal CLK. That is, the delay amount of the delay line 110 needs to be reduced.

  Thus, after the SR latch circuit 210 is reset, the SR latch circuit 210 is set when the phase determination signal PD0 becomes high level, and the change is invalidated even if the phase determination signal PD0 subsequently changes to low level. Is done. That is, if the phase determination signal PD0 becomes high level even once after the SR latch circuit 210 is set and reset, the phase determination signal PD1 that is the output of the invalidation circuit 200 is fixed at high level. . The phase determination signal PD1 becomes low level only during a period in which the phase determination signal PD0 maintains low level after the SR latch circuit 210 is reset.

  FIG. 3 is a timing chart showing the operation of the DLL circuit according to the present embodiment.

  As shown in FIG. 3, in this example, the delay amount of the delay circuit 150 is set to be slightly shorter than the sampling period. Therefore, when the update timing signal SYNCLK is activated, the reset signal RST is activated immediately after that. This means that the reset signal RST is activated immediately after the count value of the counter circuit 130 is updated.

  As shown in FIG. 3, at the timing when the reset signal RST is activated in the sampling periods T11, T13, and T15, the phase determination signal PD0 is at a high level, so the SR latch circuit 210 included in the invalidation circuit 200 is reset. Not. In this case, since the SR latch circuit 210 maintains the previous set state, even if the phase determination signal PD0 changes to a low level during the sampling period T13 as shown in the sampling period T13, such a change is invalidated. The phase determination signal PD1 maintains a high level. As a result, the count value of the counter circuit 130 is forcibly up-counted at the next timing when the update timing signal SYNCLK is activated. That is, the delay amount of the delay line 110 is forcibly increased.

  On the other hand, at the timing when the reset signal RST is activated in the sampling periods T12 and T14, the phase determination signal PD0 is at the low level, so the SR latch circuit 210 is reset in synchronization with the reset signal RST. As a result, the phase determination signal PD1 that is the output of the invalidation circuit 200 changes to a low level.

  However, in the sampling period T12, since the phase determination signal PD0 subsequently changes to the high level, the SR latch circuit 210 is set again in response thereto. As a result, the phase determination signal PD1 returns to the high level. After that, even if the phase determination signal PD0 changes to the low level within the same sampling period, such a change is invalidated and the phase determination signal PD1 maintains the high level. To do. As a result, the count value of the counter circuit 130 is forcibly up-counted at the next timing when the update timing signal SYNCLK is activated. That is, the delay amount of the delay line 110 is forcibly increased.

  On the other hand, in the sampling period T14, after the SR latch circuit 210 is reset by the activation of the reset signal RST, the phase determination signal PD0 is maintained at the low level until the next timing when the update timing signal SYNCLK is activated. . As a result, the reset state of the SR latch circuit 210 is maintained, so that the count value of the counter circuit 130 is down-counted at the next timing when the update timing signal SYNCLK is activated. That is, the delay amount of the delay line 110 is reduced.

  As described above, in this embodiment, the count value of the counter circuit 130 is down-counted in the case indicated by the sampling period T14, that is, after the SR latch circuit 210 is reset by the activation of the reset signal RST. Until the timing when the update timing signal SYNCLK is activated, the phase determination signal PD0 is limited to the case where it is maintained at the low level. In other cases, the change in the phase determination signal PD0 is invalidated by the invalidation circuit 200, and the count value of the counter circuit 130 is forcibly up-counted.

  As a result, components that affect the phase determination signal PD0 in a short cycle, such as noise and jitter components, are eliminated, so that the phenomenon that the DLL circuit 100 does not lock for a long period of time can be prevented.

  In this embodiment, since the up-counting of the counter circuit 130 is prioritized, the time required for DLL lock is shorter when the down-counting is performed (the delay amount of the replica clock signal RCLK relative to the external clock signal CLK is Even if the advance amount is larger, the DLL lock may be performed by continuing the up-counting. In this case, it takes a little longer time until DLL lock, but at least there is no problem of entering a loop that repeats up-counting and down-counting alternately, so that DLL locking is completed within the period specified by the standard. Is possible.

  Next, a second embodiment of the present invention will be described.

  FIG. 4 is a circuit diagram of the invalidation circuit 200a used in the second embodiment. This embodiment is different from the first embodiment in that the invalidation circuit 200 shown in FIG. 1 is replaced by the invalidation circuit 200a, and other points are the same. For this reason, redundant description is omitted.

  As shown in FIG. 4, the invalidation circuit 200 a includes the invalidation circuit 200 shown in FIG. 2 in that the inverter 204 is deleted and an inverter 205 that inverts the output of the SR latch circuit 210 is added. Is different. The other points are the same as the invalidation circuit 200 shown in FIG.

  With this configuration, when the phase determination signal PD0 becomes low level, the SR latch circuit 210 is set regardless of the logic level of the reset signal RST, and the phase determination signal PD1 that is the output of the invalidation circuit 200a becomes low level. On the other hand, when both the reset signal RST and the phase determination signal PD0 are at a high level, the SR latch circuit 210 is in a reset state, and the phase determination signal PD1 that is the output of the invalidation circuit 200a is at a high level.

  Thus, after the SR latch circuit 210 is reset, the SR latch circuit 210 is set when the phase determination signal PD0 becomes low level, and the change is invalidated even if the phase determination signal PD0 subsequently changes to high level. Is done. That is, if the phase determination signal PD0 is at a low level even once after the SR latch circuit 210 is set and reset, the phase determination signal PD1 that is the output of the invalidation circuit 200a is fixed at the low level. . The phase determination signal PD1 becomes high level only when the phase determination signal PD0 maintains high level after the SR latch circuit 210 is reset.

  FIG. 5 is a timing chart showing the operation of the DLL circuit according to the present embodiment.

  As shown in FIG. 5, at the timing when the reset signal RST is activated in the sampling periods T21, T23, and T25, the phase determination signal PD0 is at a low level, so the SR latch circuit 210 included in the invalidation circuit 200a is reset. Not. In this case, since the SR latch circuit 210 maintains the previous set state, even if the phase determination signal PD0 changes to a high level in the middle as shown in the sampling period T23, such a change is invalidated. The phase determination signal PD1 maintains a low level. As a result, the count value of the counter circuit 130 is forcibly down-counted at the next timing when the update timing signal SYNCLK is activated. That is, the delay amount of the delay line 110 is forcibly reduced.

  On the other hand, at the timing when the reset signal RST is activated in the sampling periods T22 and T24, the phase determination signal PD0 is at the high level, so that the SR latch circuit 210 is reset in synchronization with the reset signal RST. As a result, the phase determination signal PD1 that is the output of the invalidation circuit 200a changes to a high level.

  However, in the sampling period T22, since the phase determination signal PD0 subsequently changes to the low level, the SR latch circuit 210 is set again in response thereto. As a result, the phase determination signal PD1 returns to the low level. Thereafter, even if the phase determination signal PD0 changes to the high level within the same sampling period, such a change is invalidated, and the phase determination signal PD1 maintains the low level. To do. As a result, the count value of the counter circuit 130 is forcibly down-counted at the next timing when the update timing signal SYNCLK is activated. That is, the delay amount of the delay line 110 is forcibly reduced.

  On the other hand, in the sampling period T24, after the SR latch circuit 210 is reset by the activation of the reset signal RST, the phase determination signal PD0 is maintained at the high level until the next timing when the update timing signal SYNCLK is activated. . As a result, the reset state of the SR latch circuit 210 is maintained, so that the count value of the counter circuit 130 is up-counted at the next timing when the update timing signal SYNCLK is activated. That is, the delay amount of the delay line 110 is increased.

  As described above, in this embodiment, the count value of the counter circuit 130 is counted up in the case indicated by the sampling period T24, that is, after the SR latch circuit 210 is reset by the activation of the reset signal RST. This is limited to the case where the phase determination signal PD0 is maintained at the high level until the timing at which the update timing signal SYNCLK is activated. In other cases, the change in the phase determination signal PD0 is invalidated by the invalidation circuit 200, and the count value of the counter circuit 130 is forcibly down-counted.

  As a result, the same effects as those of the first embodiment described above can be obtained.

  In this embodiment, since the down count of the counter circuit 130 is prioritized, the time required for DLL lock is shorter when the up count is performed (the advance amount of the replica clock signal RCLK relative to the external clock signal CLK is Even in the case where the delay amount is larger), DLL lock may be performed by continuing down-counting. In this case, it takes a little longer time until DLL lock, but at least there is no problem of entering a loop that repeats up-counting and down-counting alternately, so that DLL locking is completed within the period specified by the standard. Is possible.

  Next, a third embodiment of the present invention will be described.

  FIG. 6 is a block diagram showing a configuration of a semiconductor device 30 according to the third embodiment of the present invention. In the present embodiment, both the invalidation circuits 200 and 200a are provided, and the selection circuit 31 that selects one of the invalidation circuits 200 and 200a is provided. Different from the embodiment. Since the other points are the same as those of the semiconductor device 10 according to the first embodiment, the same elements are denoted by the same reference numerals, and redundant description is omitted.

  As shown in FIG. 6, the phase determination signal PD0 that is the output of the phase determination circuit 140 is input to the selection circuit 31, and the phase determination signal PD0 obtained first after the DLL circuit 100a starts operating. One of the invalidating circuits 200 and 200a is selected on the basis of the logic level. For invalidation circuits that are not selected, the output is ignored. Specifically, when the phase determination signal PD0 obtained first is at a high level, the invalidation circuit 200 that prioritizes up-counting is selected, and when the phase determination signal PD0 obtained first is at a low level. Selects the invalidation circuit 200a that prioritizes downcounting.

  When the phase determination signal PD0 obtained first is at a high level, the time required for DLL lock is shorter when the up-count is performed (the amount of delay is greater than the amount of advance of the replica clock signal RCLK with respect to the external clock signal CLK) When the phase determination signal PD0 obtained first is at a low level, the time required for DLL lock is shorter when the down-counting is performed (replica with respect to the external clock signal CLK). The probability that the advance amount is larger than the delay amount of the clock signal RCLK) is high. Therefore, if one of the invalidation circuits 200 and 200a is selected based on the phase determination signal PD0 obtained first, the DLL circuit 100a can be made faster than the first and second embodiments described above. It can be locked.

  Next, a fourth embodiment of the present invention will be described.

  FIG. 7 is a block diagram showing a configuration of a semiconductor device 40 according to the fourth embodiment of the present invention. The present embodiment is different from the first embodiment described above in that it includes a stop circuit 41 that stops the invalidation operation of the invalidation circuit 200 described above. Since the other points are the same as those of the semiconductor device 10 according to the first embodiment, the same elements are denoted by the same reference numerals, and redundant description is omitted.

  The stop signal STP, which is the output of the stop circuit 41, is inactive in the initial state. Therefore, the invalidation circuit 200 performs the invalidation operation described above. On the other hand, the count value of the counter circuit 130 is supplied to the stop circuit 41, and when this changes in a predetermined pattern, the stop signal STP is activated. When the stop signal STP is activated, the invalidation circuit 200 stops the invalidation operation and supplies the phase determination signal PD0 as it is to the counter circuit 130 as the phase determination signal PD1.

  Here, the predetermined pattern is a pattern that appears when the DLL circuit 100b is locked or close to being locked. Specifically, it is preferable to activate the stop signal STP when a pattern of counting down after the count value of the counter circuit 130 is counted up or vice versa appears. This is because such a pattern appears when the phases of the external clock signal CLK and the replica clock signal RCLK are substantially the same. In such a case, if priority is given to the upcounting by the invalidation circuit 200, the phase may be shifted instead. Therefore, in the present embodiment, the operation of the invalidation circuit 200 is stopped by the stop circuit 41.

  Thereby, according to this embodiment, in addition to the effect by 1st Embodiment, it becomes possible to acquire the effect that the locked state after DLL lock can be maintained more reliably.

  The count value changing pattern for activating the stop signal STP may be a pattern in which up-counting and down-counting are alternately repeated three times or four times or more in addition to the above-described pattern. The reason why the up-counting and the down-counting are alternately repeated is because the characteristic is clearer when the phases of the external clock signal CLK and the replica clock signal RCLK are substantially the same.

  Next, a fifth embodiment of the present invention will be described.

  FIG. 8 is a block diagram showing a configuration of a semiconductor device 50 according to the fifth embodiment of the present invention. In the present embodiment, the delay line 110 includes a coarse delay line 111 and a fine delay line 112, a counter circuit 132 that adjusts the delay amount of the fine delay line 112, and counter circuits 130 and 132. It differs from 1st Embodiment mentioned above in the point provided with the selection circuit 51 which selects any one of these. Since the other points are the same as those of the semiconductor device 10 according to the first embodiment, the same elements are denoted by the same reference numerals, and redundant description is omitted.

  The coarse delay line 111 is a large delay line having a relatively coarse delay amount adjustment pitch, and is configured by an inverter chain in which inverters having a relatively large delay amount are cascade-connected. The fine delay line 112 is a delay line with a relatively small adjustment amount of delay amount, and is configured by an inverter chain in which inverters having relatively small delay amounts are cascade-connected or obtained from the coarse delay line 111. It is constituted by an interpolator that synthesizes two clocks.

  In the present embodiment, the delay amount of the coarse delay line 111 is adjusted by the count value of the counter circuit 130, and the delay amount of the fine delay 112 is adjusted by the count value of the counter circuit 132. The coarse delay line 111 and the fine delay line 112 are connected in series. After roughly adjusting the delay amount by the coarse delay line 111, the fine delay line 112 is used for fine adjustment of the delay amount. By doing so, a faster and more accurate DLL lock is realized.

  As shown in FIG. 8, the counter circuit 130 for controlling the coarse delay line 111 is supplied with the phase determination signal PD1 via the invalidation circuit 200, while being supplied to the counter circuit 132 for controlling the fine delay line 112. On the other hand, the phase determination signal PD0 is directly supplied. This is because the fine delay line 112 is mainly used for fine adjustment after the DLL lock, and therefore does not significantly affect the time from the unlocked state until the DLL circuit 100c is locked. This is because if the invalidating operation is performed, the possibility of phase shift increases.

  The selection circuit 51 is a circuit that permits the operation of one of the counter circuits 130 and 132 (update of the count value). The selection circuit 51 selects the counter circuit 130 in the initial state, whereby the delay line 110 performs a coarse adjustment operation by the coarse delay line 111. When the count value of the counter circuit 130 is supplied to the selection circuit 51, and this changes in a predetermined pattern, the operation of the counter circuit 130 is stopped, and instead, the counter circuit 132 is selected to select the fine delay. A fine adjustment operation by the line 112 is performed. Here, examples of the predetermined pattern include the same pattern as the pattern in which the stop signal STP is activated.

  Thus, according to the present embodiment, DLL locking can be performed at high speed, and the operation of the invalidation circuit 200 does not affect the fine delay line 112, so that a highly accurate DLL locked state is ensured. Is possible.

  Next, a sixth embodiment of the present invention will be described.

  FIG. 9 is a block diagram showing a configuration of a semiconductor device 60 according to the sixth embodiment of the present invention.

  As shown in FIG. 9, the semiconductor device 60 according to the present embodiment further includes a delay line 160, a counter circuit 170, a duty determination circuit 180, and an invalidation circuit 300. The outputs of the two delay lines 110 and 160 are signal synthesizers. The internal clock signal LCLK is generated by combining with 190. Since the other points are basically the same as those of the semiconductor device 10 according to the first embodiment described above, the same elements are denoted by the same reference numerals, and redundant description is omitted.

  Delay line 160 and counter circuit 170 constitute a duty correction circuit that corrects the duty of external clock signal CLK inverted by inverter 250. Specifically, the delay line 160 adjusts the duty of the internal clock signal LCLK by adjusting the position of the falling edge of the external clock signal CLK. The adjustment amount is determined by the counter circuit 170. On the other hand, the delay line 110 adjusts the phase of the internal clock signal LCLK by adjusting the position of the rising edge of the external clock signal CLK. As a result, the internal clock signal LCLK generated by the signal synthesizer 190 is a signal whose phase and duty are correctly adjusted.

  The counter circuit 170 is a circuit for setting the delay amount of the delay line 160, and its count value is updated in synchronization with the update timing signal SYNCLK. The increase / decrease of the count value is determined based on the duty determination signal DD1 supplied from the invalidation circuit 300. That is, when the duty determination signal DD1 indicates an up count, the counter circuit 170 counts up the count value in synchronization with the update timing signal SYNCLK, thereby increasing the delay amount of the delay line 160. Conversely, when the duty determination signal DD1 indicates a down count, the counter circuit 170 counts down the count value in synchronization with the update timing signal SYNCLK, thereby reducing the delay amount of the delay line 160.

  The invalidation circuit 300 is a circuit that receives the duty determination signal DD0 and the reset signal RST and generates the duty determination signal DD1 based on them. The circuit configuration is the same as that of the invalidation circuit 200 shown in FIG. 2 or the invalidation circuit 200a shown in FIG. Therefore, the invalidation circuit 300 performs the invalidation operation similar to the invalidation circuit 200 or 200a.

  The duty determination circuit 180 is a circuit that detects the duty of the internal clock signal LCLK based on the outputs of the delay lines 110 and 160 and thereby generates the duty determination signal DD0.

  As described above, the DLL circuit 100d according to the present embodiment uses the invalidation circuit 200 to eliminate components that affect the phase determination signal PD0 in a short cycle, such as noise and jitter components, and generate the duty determination signal DD0 in a short cycle. The influencing component is excluded by the invalidation circuit 300. For this reason, not only the phase but also the duty can be quickly adjusted.

  The preferred embodiments of the present invention have been described above, but the present invention is not limited to the above-described embodiments, and various modifications can be made without departing from the spirit of the present invention. Needless to say, it is included in the range.

  For example, in each of the above embodiments, the case where the present invention is applied to a DLL circuit has been described as an example. However, the application target of the present invention is not limited to this, and other types of clock control circuits such as duty correction It is also possible to apply to a circuit (see FIG. 9).

  In each of the above embodiments, the invalidation circuit 200 and the like are reset using the reset signal RST. However, the update timing signal SYNCLK itself may be used as the reset signal RST as long as it does not interfere with the update operation of the counter circuit 130. I do not care. Further, the reset signal RST may be generated by delaying the update timing signal SYNCLK.

10, 30, 40, 50, 60 Semiconductor device 11 Internal circuit 12 Output buffer 13 Output terminal 14 Clock terminal 15 Replica buffer 31 Selection circuit 41 Stop circuit 51 Selection circuit 100, 100a, 100b, 100c, 100d DLL circuit 110, 160 Delay Line 111 Coarse delay line 112 Fine delay line 120 Divider circuits 130, 132, 170 Counter circuit 140 Phase determination circuit 150 Delay circuit 180 Duty determination circuit 190 Signal combiner 200, 200a, 300 Invalidation circuit 210 SR latch circuit

Claims (5)

A phase determination circuit that generates a first phase determination signal that varies between a first logic level and a second logic level based on a phase difference between the first clock signal and the second clock signal;
Upon receiving the second phase determination signal, the sampling operation of the second phase determination signal is performed in a cycle longer than the cycle of the first clock signal, and the second phase determination signal in the first state is sampled. A counter circuit that increments the count value if it is, and decrements the count value when the second phase determination signal in the second state is sampled;
A delay line that generates an intermediate clock signal by delaying the first clock signal based on the count value of the counter circuit;
A buffer circuit for generating a second clock signal based on the intermediate clock signal;
A generation circuit that is provided between the phase determination circuit and the counter circuit and generates the second phase determination signal in response to the first phase determination signal;
Within the interval of adjacent sampling operations by the counter circuit, the first phase determination signal changes a first number of times between the first logic level and the second logic level, and the second phase determination signal the least for the second number varies than or equal the first number and the first number between the first state and the second state,
The counter circuit receives an update timing signal, the generation circuit receives a reset signal, the update timing signal determines a cycle of the sampling operation, and the reset signal is a signal having the same cycle as the update timing signal and a different phase And
The generation circuit includes an SR latch circuit, and the SR latch circuit is set when the first phase determination signal is one of the first and second logic levels, and the first phase determination signal is the first. And the second logic level is reset when the reset signal is applied, and the SR latch circuit generates the second phase determination signal . The SR latch circuit includes a set terminal, a reset terminal, and an output terminal, and a first inverter circuit that receives the first phase determination signal is connected to the set terminal, and a second signal that receives the reset signal. of the inverter circuit is connected to the reset terminal, the semiconductor device according to claim 1, wherein the outputting the second phase judgment signal from the output terminal. The SR latch circuit includes a set terminal, a reset terminal, and an output terminal. The first phase determination signal is input to the set terminal, and a first inverter circuit that receives the reset signal is connected to the reset terminal. is, the semiconductor device according to claim 1, wherein the output of the second inverter circuit, wherein the output terminal of the SR latch circuits connected to the input is in the second phase judgment signal. Said intermediate operates in response to the clock signal, further comprising another buffer circuit, a semiconductor device according the another buffer circuit to any one of claims 1 to 3, characterized in that the same configuration as the buffer circuit . A divider circuit wherein a first clock signal by dividing to generate the reset signal, from claim 1, further comprising a delay circuit connected to said divider circuit generates the update timing signal 3 The semiconductor device according to any one of the above.

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