JP5438281B2 - Receiver for distance measuring device and distance measuring device - Google Patents

Description

  The present invention relates to a distance measurement device that measures a distance to a distance measurement target by transmitting and receiving a radio signal, and a receiver mounted on the distance measurement device.

  A distance measuring device for measuring a distance to a wireless tag by transmitting / receiving a wireless signal to / from the wireless tag has been developed. The distance measuring device transmits a radio pulse signal when measuring the distance. The wireless tag receives the wireless pulse signal, and generates and transmits a response signal for the wireless pulse signal. The distance measuring device receives the wireless response signal, and measures the distance to the wireless tag based on the difference between the transmission timing of the wireless pulse signal and the reception timing of the wireless response signal and the propagation speed of the wireless signal.

  Here, the radio pulse signal and the radio response signal are pulse modulation signals obtained by multiplying a pulse signal such as a rectangular single pulse signal by a sine wave signal or the like. The difference between the transmission timing of the radio pulse signal and the reception timing of the radio response signal can be obtained based on the difference in the envelope change timings of these pulse modulation signals and the phase difference between these pulse modulation signals.

JP 2006-145222 A

  The distance measuring device converts the radio response signal into a baseband I / Q signal composed of an in-phase component signal I and a quadrature component signal Q by multiplying the received radio response signal by a local signal. Then, a distance measurement signal is generated based on the baseband I / Q signal, and the distance to the wireless tag is measured based on the generation timing of the distance measurement signal and the transmission timing of the wireless pulse signal.

  When distance measurement is performed based on the transmission antenna position and the reception antenna position of the distance measurement device, the transmission timing of the radio pulse signal is the timing at which the radio pulse signal is transmitted from the transmission antenna. The reception timing of the wireless response signal is set to a timing at which the wireless response signal is received by the receiving antenna. Therefore, when distance measurement is performed based on the difference between the phase of the radio pulse signal and the phase of the distance measurement signal, the amount of phase change from the generation of the radio pulse modulation signal to the transmission antenna and the reception It is necessary to consider the amount of phase change from when the radio response signal is received by the antenna to when the distance measurement signal is generated.

An object of the present invention is to improve distance measurement accuracy in a distance measurement device that measures a distance to a distance measurement target by transmitting and receiving radio signals.

The present invention includes a local signal generation unit that generates a local signal, a signal generation unit that generates a radio pulse signal having a phase corresponding to the phase of the local signal, a transmission unit that transmits the radio pulse signal, and the transmission A reception unit that receives a radio response signal from a distance measurement target that has responded to a signal transmitted from the unit; a quadrature detection unit that performs quadrature detection processing on the signal received by the reception unit using the local signal; the process of separating a desired signal multipath environment from propagating to the received signal, and a separation processing unit that performs relative quadrature detection signals generated by the quadrature detection section, separated by the separation processing unit separating The signal is subjected to quadrature modulation processing based on the local signal, and the initial phase of the local signal that has been included by the quadrature detection processing is canceled out. A quadrature modulator for outputting a phase difference distance measurement signal, said separation signal is added to the transmission timing of the timing output from the separating processing unit and the radio pulse signal, the phase difference distance output from the quadrature modulation unit A distance measurement unit that obtains a distance to the distance measurement target based on a value indicating a phase difference between the measurement signal and the wireless pulse signal;

In addition, the present invention has a transmission antenna that transmits a radio signal, a plurality of unit antennas that each receive the radio signal, a local signal generation unit that generates a local signal, and a phase corresponding to the phase of the local signal A signal generation unit that generates a radio pulse signal, a transmission unit that transmits the radio pulse signal from the transmission antenna, and a distance that is provided corresponding to each unit antenna and responds to a signal transmitted from the transmission antenna A reception unit that receives a radio response signal from a measurement target via a corresponding unit antenna, and a quadrature detection process using the local signal for a signal that is provided for each reception unit and received by the corresponding reception unit. And a directivity control process for controlling the reception directivity characteristics of the plurality of unit antennas provided corresponding to each orthogonal detection unit, A directivity control unit for performing relative quadrature detection signals generated by the quadrature detection unit, and a synthesizing unit for synthesizing the quadrature detection signal the directivity control process is performed with respect to the combined signal, wherein the combining unit outputs A quadrature modulation unit that performs quadrature modulation processing based on the local signal and outputs a phase difference distance measurement signal in which an initial phase of the local signal that has been included by the quadrature detection processing is canceled, and the combined signal Is based on a value indicating a phase difference between the phase difference distance measurement signal output from the quadrature modulation unit and the radio pulse signal in addition to the timing output from the synthesis unit and the transmission timing of the radio pulse signal. And a distance measuring unit for obtaining a distance to the distance measuring target.

  According to the present invention, the distance measurement accuracy of the distance measuring device can be increased.

  FIG. 1 shows a configuration of a wireless tag distance measuring system according to an embodiment of the present invention. In this system, the wireless tag distance measuring device 10 measures the distance to the wireless tag by transmitting and receiving wireless signals to and from the wireless tag. A unique PN code (PN is an abbreviation of Pseudo Noise) is assigned to the wireless tags 12-1 to 12-4. In FIG. 1, “01001...”, “10011...”, “01111...” And “10001. "Is assigned. The wireless tag distance measuring device 10 specifies a wireless tag as a distance measurement target by a PN code.

  In general, a PN code indicates a pseudo-noise pattern due to 1 and 0. By associating the signal values “1” and “−1” with the values “1” and “0” of the PN code, respectively, it is possible to generate a PN signal whose value changes with the pattern of the PN code. When the diffusion process for performing the convolution operation between the PN signal and the processing target signal is performed, the time length of the processing target signal is spread according to the time length of the PN signal. For such a spread signal, the original signal can be reproduced by performing a despreading process that performs a convolution operation with the PN signal used in the spreading process. In addition, an original signal can be extracted by despreading processing from a signal obtained by adding a plurality of spread signals subjected to spreading processing using different PN codes. The RFID tag distance measurement system according to the present embodiment uses such orthogonality of PN codes.

  When measuring the distance to a wireless tag as a distance measurement target, the wireless tag distance measuring device 10 generates a pulse modulation signal obtained by multiplying a sine wave signal by a pulse signal such as a rectangular single pulse signal. Then, spreading processing is performed on the pulse modulated signal by using the uniquely assigned PN code of the wireless tag to be measured for distance, and the spread pulse modulated signal is transmitted.

  Among the plurality of wireless tags that have received the spread pulse modulated signal, the wireless tag in which the PN code used for the spread processing of the spread pulse modulated signal and its own uniquely assigned PN code matches the received spread pulse modulated signal. Then, a response pulse modulation signal subjected to despreading processing is transmitted.

  Upon receiving the response pulse modulation signal, the wireless tag distance measurement device 10 calculates the distance to the wireless tag to be measured based on the time from when the spread pulse modulation signal is transmitted until the response pulse modulation signal is received. calculate.

  FIG. 2 shows the configuration of the RFID tag distance measuring apparatus 10 for executing such processing. Further, FIG. 3 shows the configuration of the transmission unit 14 which is one component of the RFID tag distance measuring apparatus 10. Of the components of the wireless tag distance measuring apparatus 10, the component subsequent to the A / D converter 34 is assumed to process a digital signal obtained by digitally sampling the signal to be processed. Of the components of the transmitter 14, the components upstream of the D / A converter 24 are assumed to process digital signals.

  The local signal generator 40 outputs the local signal to the pulse modulation signal generator 16. The pulse modulation signal generation unit 16 generates a pulse modulation signal obtained by multiplying the local signal by the pulse signal, and outputs the pulse modulation signal to the diffusion processing unit 18 and the distance calculation unit 48.

  The PN code storage unit 20 stores a unique assignment PN code of a wireless tag used in the wireless tag distance measurement system. When a wireless tag to be measured for distance is designated by a user operation or a device provided separately, the code selection unit 22 reads the specific assigned PN code of the designated wireless tag from the PN code storage unit 20. Then, a PN signal is generated based on the read PN code and output to the diffusion processing unit 18.

  The spread processing unit 18 generates a spread pulse modulation signal obtained by performing spread processing on the pulse modulation signal using the PN signal output from the code selection unit 22 and outputs the spread pulse modulation signal to the D / A converter 24. The D / A converter 24 converts the spread pulse modulation signal output from the spread processing unit 18 into an analog signal and outputs the analog signal to the radio transmission unit 26. The wireless transmission unit 26 converts the spread pulse modulated signal into a wireless signal and transmits it through the transmission antenna 28.

  By such processing, the phase is determined based on the phase of the local signal, and the spread pulse modulated signal that has been spread by the PN code designated by the code selection unit 22 is transmitted from the RFID tag distance measuring device 10. .

  The spread pulse modulated signal transmitted from the wireless tag distance measuring device 10 is received by each wireless tag. FIG. 4A shows the configuration of the wireless tag 12. The spread pulse modulated signal received by the wireless tag antenna 54 is input to the duplexer 56. The duplexer 56 outputs the pulse modulated signal to the correlation processing device 58. The duplexer 56 can be configured using a circulator, a directional coupler, or the like.

  As the correlation processing device 58 of the wireless tag 12, a device that performs a convolution operation on the input signal and outputs it using a PN code uniquely assigned to the wireless tag 12 is used. As such a device, a SAW device, a CCD (Charge Coupled Device) matched filter, a digital matched filter, or the like can be used. Some SAW devices require supply power (such as SAW convolvers) and others do not require supply power. When a SAW device that does not need to supply power is used, it is not necessary to mount a power supply source on the wireless tag 12.

  In addition, a digital matched filter, a SAW convolver, and the like can arbitrarily set a PN code when performing a convolution operation. The configuration in this case is shown in FIG. Here, the case where the digital matched filter 58A is used is shown. When a SAW convolver is used, the digital matched filter 58A may be replaced with a SAW convolver. The wireless tag 12 is provided with a PN code storage unit 60 for storing a PN code and a PN code setting circuit 62. The PN code storage unit 60 stores a plurality of different PN codes in advance. The PN code setting circuit 62 reads the PN code from the PN code storage unit 60, and sets the operation state of the digital matched filter 58A so that the digital matched filter 58A executes processing based on the PN code. Further, instead of providing the PN code storage unit 60 and the PN code setting circuit 62, a configuration may be adopted in which a PN code is set in the digital matched filter 58A by a device outside the wireless tag 12. According to the configuration of the wireless tag 12 using the digital matched filter 58A, it is possible to share hardware for a plurality of wireless tags 12 to which different PN codes are given.

  The correlation processing device 58 performs a convolution operation on the signal output from the duplexer 56 using the unique assignment PN code of the wireless tag 12 and outputs the result to the duplexer 56. The duplexer 56 outputs the signal output from the correlation processing device 58 to the RFID tag antenna 54. A signal output from the duplexer 56 is transmitted from the wireless tag antenna 54.

  In the case where the signal input to the correlation processing device 58 is a signal that has been subjected to spreading processing using the uniquely assigned PN code, the correlation processing device 58 before the spreading processing that has been subjected to despreading processing on the input signal. Is output. On the other hand, when the signal input to the correlation processing device 58 is a signal that has been subjected to spreading processing using a code different from the uniquely assigned PN code, the signal before spreading processing is not output from the correlation processing device 58. .

  Therefore, when the spread pulse modulated signal received by the RFID tag antenna 54 is a signal that has been spread by the uniquely assigned PN code, the correlation processing device 58 performs despread processing on the spread pulse modulated signal. The signal before spreading processing is output. As a result, among the plurality of wireless tags, the wireless tag in which the original PN code obtained by performing the spreading process on the received spread pulse modulated signal and the own unique assigned PN code match the spread pulse modulated signal. Then, the signal subjected to the despreading process is transmitted as a response pulse modulation signal.

  Next, processing performed by the wireless tag distance measuring device 10 for the response pulse modulation signal transmitted from the wireless tag will be described. The wireless tag distance measuring device 10 includes a plurality of unit antennas 30 that constitute an adaptive array antenna. Each unit antenna 30 receives the response pulse modulation signal and inputs it to the corresponding radio reception unit 32. Each radio reception unit 32 amplifies the response pulse modulated signal received by the unit antenna 30 until it reaches a predetermined signal level, and outputs the amplified signal to the corresponding A / D converter 34. Each A / D converter 34 converts the signal output from the wireless receiver 32 into a digital signal and outputs the digital signal to the corresponding quadrature detector 36.

  The local signal generator 40 outputs a local signal to each quadrature detector 36 in addition to the pulse modulation signal generator 16. Each quadrature detector 36 extracts the in-phase component signal I and the quadrature component signal Q from the signal output from the A / D converter 34 by the local signal, and outputs them to the weight multiplier 38. The in-phase component signal I is a signal obtained by extracting a component having the same phase relationship as the local signal from the output signal of the A / D converter 34, and the quadrature component signal Q has a phase difference of 90 ° with respect to the local signal. This is a signal obtained by extracting the component from the output signal of the A / D converter 34.

  Each weight multiplier 38 is obtained for each of the in-phase component signal I and the quadrature component signal Q by the directivity control unit 42 for each of the in-phase component signal I and the quadrature component signal Q output from the quadrature detector 36. The weighting factor is multiplied and output to the combining unit 44.

  The synthesizing unit 44 adds and sums the weighted in-phase component signal Iw obtained by adding and summing the in-phase component signals processed by each weight multiplying unit 38 and the quadrature component signal processed by each weight multiplying unit 38. The weight-processed quadrature component signal Qw is output to the distance calculation unit 48, the reverse rotation quadrature modulator 50, and the directivity control unit 42.

  According to such a process, the total directivity characteristic determined by all the unit antennas 30 is determined by the weight coefficient output from the directivity control unit 42. Then, the weight-processed in-phase component signal Iw and the weight-processed quadrature component signal Qw output from the combining unit 44 are signals received with the total directional characteristics.

The directivity control unit 42 calculates a weight coefficient so that the maximum directivity characteristic direction coincides with the arrival direction of the response pulse modulation signal, and outputs the calculated weight coefficient to each weight multiplication unit 38. This processing can be performed, for example, by an adaptive algorithm that converges the weight coefficient so that the ratio of the in-phase component signal Iw after the weight processing and the quadrature component signal Qw after the weight processing to each noise becomes the largest.
In addition, adaptive signal processing for estimating the arrival direction of the desired signal may be used for the processing for calculating the weight coefficient. MMSE, MUSIC, etc. are widely known as such adaptive signal processing. When a multipath exists between the wireless tag distance measuring device 10 and the wireless tag, there are a plurality of paths from the wireless tag to the wireless tag distance measuring device 10. When measuring the distance to the wireless tag in such a multipath environment, it is preferable to use a response pulse modulated signal transmitted from the wireless tag and coming directly from a plurality of signals having different arrival directions. Therefore, it is preferable to execute the process of estimating the arrival direction of the response pulse modulation signal that arrives directly by MMSE, MUSIC, or the like, and calculating the weight coefficient so that the maximum directionality characteristic coincides with the arrival direction. Thereby, a signal suitable for distance measurement can be separated from a plurality of signals having different arrival directions. By using the adaptive signal processing for estimating the direction of arrival in this embodiment, it is possible to reduce the influence of the response pulse modulated signal due to the multipath environment and improve the measurement accuracy of the distance to the wireless tag.

  The directivity control unit 42 further obtains a weight phase change amount generated by the weight coefficient multiplication process, and outputs it to the distance calculation unit 48. The weight phase change amount is generated by weight coefficient multiplication processing on the Iw / Qw plane vector phase angle when the value of the in-phase component signal Iw after weight processing is on the horizontal axis and the value of the quadrature component signal Qw after weight processing is on the vertical axis. Indicates the amount of phase change.

  The local signal generation unit 40 outputs a local signal to the reverse rotation processing unit 46 in addition to the pulse modulation signal generation unit 16 and each quadrature detector 36. The reverse rotation processing unit 46 generates a reverse rotation local signal obtained by inverting the polarity of the phase time change of the local signal and outputs the reverse rotation local signal to the reverse rotation quadrature modulator 50. For example, when the amplitude of the local signal is A, the angular frequency is ω, the time is t, and the initial phase is φ, the local signal is represented as Aexp [j (ωt + φ)] in a complex expression. At this time, the reverse rotation local signal is expressed as Aexp [−j (ωt + φ)]. When a complex signal converted into a digital signal is used as the local signal, a reverse rotation local signal can be generated by obtaining a conjugate complex number of the local signal.

  The reverse rotation quadrature modulator 50 generates a phase difference distance measurement signal by performing quadrature modulation processing on the in-phase component signal Iw after weight processing and the quadrature component signal Qw after weight processing, using the reverse rotation local signal, It outputs to the distance calculation part 48.

In the RFID tag distance measuring apparatus 10 according to the present embodiment, the in-phase component signal I and the quadrature component signal Q are extracted from the output signal of each A / D converter 34 using the local signal. The local signal is Aexp [j (ωt + φ)], the in-phase component signal I output from each quadrature detector 36 is taken on the horizontal axis, and the quadrature component signal Q outputted from each quadrature detector 36 is taken on the vertical axis. the I / Q plane vector phase angle, Ru contains an initial phase φ of the local signal outputted from the local signal generator 40 to the quadrature detector 36. Thus, also in Iw / Qw plane vector phase angle of the wait process after in-phase component signal Iw and weight processing the quadrature component signal Qw, Ru include the initial phase phi.

In the present embodiment, quadrature modulation processing using a reverse rotation local signal is performed on the in-phase component signal Iw after weight processing and the quadrature component signal Qw after weight processing to generate a phase difference distance measurement signal. Thus, if the processing accuracy of each component is sufficient, the initial phase included in the Iw / Qw plane vector phase angle can be canceled by the initial phase of the reverse rotation local signal. As a result, the influence of the initial phase of the local signal output from the local signal generator 40 to each quadrature detector 36 on the phase difference distance measurement signal can be reduced, and the measurement measured by the process described below. It is possible to avoid an error in the distance.

Then, the distance calculation unit 48, pulse modulation signal, the wait process after in-phase component signal Iw and weight processing the quadrature component signal Qw, and the process of obtaining the distance to the wireless tag by using the phase difference distance measurement signal is described .

  The distance calculation unit 48 obtains the sum of squares of the in-phase component signal Iw after the weight processing and the quadrature component signal Qw after the weight processing, and further obtains the envelope of the square root of the sum of the squares as the received envelope signal. The distance calculation unit 48 obtains the envelope of the pulse modulation signal output from the pulse modulation signal generation unit 16 as a transmission envelope signal.

  The distance calculation unit 48 measures the difference between the rise time of the transmission envelope signal and the rise time of the reception envelope signal. Then, based on the measured time difference, a round-trip propagation time when the wireless signal reciprocates between the wireless tag distance measuring device 10 and the wireless tag is obtained, and the wireless tag is based on the round-trip propagation time and the propagation speed of the wireless signal. The round-trip distance (twice the distance to the wireless tag) is calculated as the round-trip envelope distance.

  When calculating the round-trip propagation time, the distance calculation unit 48 determines the delay time from when the signal is output from the pulse modulation signal generation unit 16 to the transmission antenna 28, the reception / transmission response time of the wireless tag, and the signal The delay time from reception by the unit antenna 30 to output from the combining unit 44 is subtracted from the difference between the transmission envelope signal rise time and the reception envelope signal rise time. As a result, the round-trip distance based on the positions of the transmission antenna 28 and the unit antenna 30 can be calculated. These delay times are times unique to the RFID tag distance measuring device 10 and the RFID tag, and can be obtained in advance at the design stage.

  The reciprocal envelope distance thus obtained includes a resolution error corresponding to the measurement resolution. That is, the true reciprocal distance is between the distance obtained by subtracting the resolution error from the reciprocal envelope distance and the distance obtained by adding the resolution error to the reciprocal envelope distance. This resolution error depends on the relationship between the frequency of the sine wave signal that generated the pulse modulation signal and the pulse time length of the pulse modulation signal, the characteristics of the components of the RFID tag distance measuring device 10, the characteristics of the RFID tag, and the like. This is a fixed value and can be obtained at the design stage.

  Therefore, according to such a process, it is possible to obtain a round trip distance in which an error corresponding to the resolution error is expected on the plus side and the minus side with the round trip envelope distance as the center. The distance calculation unit 48 may set half of the reciprocal envelope distance as the measurement distance, output the information to the display unit 52, and display the measurement distance on the display unit 52.

The wireless tag distance measuring apparatus 10 according to the present embodiment, by using the phase difference distance measurement signals output from the reverse rotation quadrature modulator 50, it is possible to improve the distance measurement accuracy. However, the measurement accuracy processing using a phase difference distance measurement signal, so that twice the resolution of the error than the propagation wavelength of an electromagnetic wave having a frequency of the original sine wave signal to generate a pulse modulation signal becomes shorter, the radio tag A distance measuring system is preferably designed. In this embodiment, it is assumed that such a design is made. It shows a flowchart of a process using the phase difference distance measurement signal in FIG.

  The distance calculation unit 48 obtains a phase difference between the pulse modulation signal output from the pulse modulation signal generation unit 16 and the phase difference distance measurement signal as a measurement phase difference (S101). Further, the distance calculation unit 48 outputs the pulse modulation signal from the pulse modulation signal generation unit 16 and outputs the phase change amount to the transmission antenna 28, the phase change amount based on the reception / transmission response of the wireless tag, and the response pulse modulation signal. For distance measurement, which is received by the unit antenna 30 and reaches the distance calculation unit 48 as a phase difference distance measurement signal, the phase change amount excluding the weight phase change amount and the weight phase change amount is subtracted from the measured phase difference. The phase difference P is obtained (S102).

  These phase change amounts excluding the weight phase change amount are specific to the RFID tag distance measuring device 10 and the RFID tag, and can be obtained in advance at the design stage. Further, the weight phase change amount is output from the directivity control unit 42 in accordance with the above-described processing for obtaining the weight coefficient.

  The distance calculation unit 48 obtains a lower limit value d1 obtained by subtracting the resolution error from the round-trip envelope distance and an upper limit value d2 obtained by adding the resolution error to the round-trip envelope distance (S103). Further, the distance calculation unit 48 obtains an integer (an integer part) obtained by rounding down the decimal point of the value obtained by dividing the lower limit value d1 by the sine wave wavelength λ as m (S104). A value obtained according to D1 = λ (2mπ + P) / (2π) is set as the first estimated round-trip distance D1 (S105). Here, the sine wave wavelength λ is the propagation wavelength of the electromagnetic wave having the frequency of the original sine wave signal that generated the pulse modulation signal.

  The distance calculation unit 48 obtains an integer obtained by rounding down the decimal point of the value obtained by dividing the upper limit value d2 by the sine wave wavelength λ as n (S106). Then, a value obtained according to D2 = λ (2nπ + P) / (2π) is set as the second estimated round-trip distance D2 (S107).

  The distance calculation unit 48 determines whether or not the first estimated round trip distance D1 and the second estimated round trip distance D2 are equal (S108). If these values are equal, half of the first estimated round trip distance D1 or half of the second estimated round trip distance D2 is determined as the measurement distance to the wireless tag (S109), and the measurement distance information is output to the display unit 52. (S111). The display unit 52 displays the measurement distance.

  When the first estimated round-trip distance D1 and the second estimated round-trip distance D2 are different, the distance calculation unit 48 determines the half of the distance between the lower limit value d1 and the upper limit value d2 among these round-trip distances as a wireless tag. (S110) and output to the display unit 52 (S111). The display unit 52 displays the measurement distance.

  According to steps S101 and S102, the difference between the phase of the pulse modulation signal transmitted from the transmission antenna 28 and the phase of the response pulse modulation signal received by each unit antenna 30 is obtained as the distance measurement phase difference P. it can. The distance measurement phase difference P takes a value from 0 to 2π. This value represents the propagation phase change amount corresponding to the decimal point when the round-trip distance to the wireless tag is expressed in wavelength units. Therefore, by calculating the number of wavelengths of the integer part when the round-trip distance to the wireless tag is expressed in wavelength units based on the round-trip envelope distance, The round trip distance between can be determined.

  The round trip distance to the wireless tag can be expressed as 2πj + P in terms of phase, where j is an integer obtained by rounding off the round trip distance divided by the sine wave wavelength λ. When this is converted into a distance unit, it is λ (2πj + P) / (2π).

  This integer j is either integer m or integer n. Here, the integer m obtained in step S104 is an integer part when the lower limit value d1 is expressed in wavelength units, and the integer n obtained in step S106 is an integer part when the upper limit value d2 is expressed in wavelength units. It is. As described above, the RFID tag distance measurement system is designed so that twice the resolution error is shorter than the propagation wavelength of the electromagnetic wave having the sinusoidal signal frequency. Therefore, these integers are equal or different from each other, and either n = m or n = m + 1 holds. Therefore, the round-trip distance to the wireless tag is D1 = D2 when n = m, and is either D1 or D2 when n = m + 1.

  The round-trip distance to the wireless tag is between the lower limit value d1 and the upper limit value d2. Therefore, when n = m + 1, that is, when the first estimated round-trip distance D1 and the second estimated round-trip distance D2 are different, select one of these values that is between the lower limit value d1 and the upper limit value d2. Thus, the distance to the wireless tag may be determined. Steps S108 to S110 determine the distance to the wireless tag based on such a principle.

It is a figure which shows the structure of a radio | wireless tag distance measurement system. It is a figure which shows the structure of a wireless tag distance measuring apparatus. It is a figure which shows the structure of a transmission part. It is a figure which shows the structure of a wireless tag. It is a flowchart of the process using the signal for phase difference distance measurement.

Explanation of symbols

  10 wireless tag distance measuring device, 12-1 to 12-4 wireless tag, 14 transmission unit, 16 pulse modulation signal generation unit, 18 spreading processing unit, 20, 60 PN code storage unit, 22 code selection unit, 24 D / A Converter, 26 radio transmission unit, 28 transmission antenna, 30 unit antenna, 32 radio reception unit, 34 A / D converter, 36 orthogonal detector, 38 weight multiplication unit, 40 local signal generation unit, 42 directivity control unit, 44 combining unit, 46 reverse rotation processing unit, 48 distance calculation unit, 50 reverse rotation quadrature modulator, 52 display unit, 54 RFID tag antenna, 56 demultiplexer, 58 correlation processing device, 58A digital matched filter, 62 PN code setting circuit.

Claims (2)

A local signal generator for generating a local signal;
A signal generator that generates a radio pulse signal having a phase corresponding to the phase of the local signal;
A transmitter for transmitting the radio pulse signal;
A receiver that receives a radio response signal from a distance measurement target that responds to the signal transmitted from the transmitter;
A quadrature detection unit that performs quadrature detection processing on the signal received by the reception unit using the local signal;
A separation processing unit that performs processing on a quadrature detection signal generated by the quadrature detection unit for separating a desired signal from signals received through propagation in a multipath environment;
For phase difference distance measurement in which quadrature modulation processing based on the local signal is performed on the separated signal separated by the separation processing unit, and the initial phase of the local signal that has been included by the quadrature detection processing is canceled out A quadrature modulation unit for outputting a signal;
In addition to the timing at which the separated signal is output from the separation processing unit and the transmission timing of the radio pulse signal, the phase difference between the phase difference distance measurement signal output from the quadrature modulation unit and the radio pulse signal is calculated. A distance measuring unit that obtains a distance to the distance measurement target based on the indicated value;
A distance measuring device comprising: A transmitting antenna for transmitting radio signals;
A plurality of unit antennas each receiving a radio signal;
A local signal generator for generating a local signal;
A signal generator that generates a radio pulse signal having a phase corresponding to the phase of the local signal;
A transmitter for transmitting the radio pulse signal from the transmitting antenna;
A reception unit that is provided corresponding to each unit antenna and receives a radio response signal from a distance measurement target that responds to a signal transmitted from the transmission antenna via the corresponding unit antenna;
A quadrature detection unit that is provided corresponding to each reception unit, and that performs quadrature detection processing by the local signal with respect to a signal received by the corresponding reception unit;
A directivity control processing unit that is provided corresponding to each quadrature detection unit and that performs a directivity control process for controlling reception directivity characteristics by the plurality of unit antennas on the quadrature detection signal generated by each quadrature detection unit; ,
A synthesis unit that synthesizes the quadrature detection signal subjected to the directivity control processing;
A phase difference distance measurement signal in which an orthogonal modulation process based on the local signal is performed on the combined signal output from the combining unit, and an initial phase of the local signal that has been included by the orthogonal detection process is canceled. An output quadrature modulation unit;
In addition to the timing at which the synthesized signal is output from the synthesizing unit and the transmission timing of the radio pulse signal, the phase difference distance measurement signal output from the quadrature modulation unit and the phase difference between the radio pulse signal are indicated. A distance measurement unit for obtaining a distance to the distance measurement target based on the value;
A distance measuring device comprising:

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