JP5326444B2 - Rotating machine control device - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To solve the problem that controllability of a motor generator is deteriorated in a high torque region in field-weakening control. <P>SOLUTION: A field-weakening control section 200 has a q-axis current operation section 210 and a d-axis current operation section 220. The q-axis current operation section 210 sets a command current iqr as an operation quantity for feedback-controlling an estimated torque Te to a request torque Tr, and sets a command voltage vdr as an operation quantity for feedback-controlling an actual current iq to a command current iqr. On the contrary, the d-axis current operation section 220 sets a command current idr as an operation quantity for feedback-controlling the estimated torque Te to the request torque Tr, and sets a command voltage vdr as an operation quantity for feedback-controlling the actual current id to the command current idr. The control by the q-axis current operation section 210 and the control by the d-axis current operation section 220 are switched depending on a torque. <P>COPYRIGHT: (C)2010,JPO&amp;INPIT

Description

  The present invention relates to a control apparatus for a rotating machine that sets a command voltage of a two-dimensional coordinate system in accordance with the command value and controls a power conversion circuit based on the command value in order to control the control amount of the rotating machine to the command value. .

As this type of control device, for example, as shown in Non-Patent Document 1 below, feedback control is performed on the current actually flowing on the q-axis of the motor to a q-axis command current set according to the torque command value. Therefore, there has been proposed one for manipulating the phase of the command voltage vector on the dq axis. Thus, torque control with high responsiveness of the motor can be realized in a region where the voltage utilization rate is high.
Oi, Tobari, Iwaji, "Voltage phase manipulation type field weakening control method realizing high response", 2007 IEEJ Industrial Application Conference

  However, when the torque is controlled by manipulating the q-axis current as described above, the inventors have found that the controllability decreases as the torque increases, and in some cases, the control may fail. It was.

  The present invention has been made in order to solve the above-described problems, and an object of the present invention is to provide a control device for a rotating machine that can suitably control a control amount of the rotating machine based on its command value.

  Hereinafter, means for solving the above-described problems and the operation and effects thereof will be described.

A first invention is a control device for a rotating machine that controls a control amount of the rotating machine by operating a power conversion circuit including a switching element that connects a terminal of the rotating machine to each of a positive electrode and a negative electrode of a DC power supply. By setting the command voltage of the two-dimensional coordinate system based on the command current of the orthogonal component with respect to the magnetic pole direction of the rotating machine and the input voltage of the power conversion circuit, the control amount is based only on the command current of the orthogonal component. By setting the command voltage of the two-dimensional coordinate system based on the orthogonal direction current operation means for controlling the magnetic field, the command current of the magnetic pole direction component of the rotating machine and the input voltage of the power conversion circuit, Magnetic pole direction current operation means for controlling the control amount based only on the command current, and when the torque of the rotating machine exceeds a predetermined value, control by the orthogonal direction current operation means Characterized in that it comprises a priority means for giving priority to the control by the magnetic pole direction current operation means.

  In the high torque region, when the torque changes suddenly with respect to the change in the orthogonal component, and the torque becomes very large, the one-to-one correspondence between the orthogonal component current and the torque is lost. It has been found by the inventors. For this reason, in the area | region where the torque of a rotary machine is large, there exists a possibility that the controllability by an orthogonal direction current operation means may fall. On the other hand, the current and torque in the magnetic pole direction component have a one-to-one correspondence in the high torque region, and the degree of change in torque with respect to the change in current in the magnetic pole direction component is also in accordance with the change in current in the orthogonal direction component. It is moderate compared to the degree of change in torque. In the above invention, in view of this point, when the torque is equal to or greater than a predetermined value, priority is given to the control by the magnetic pole direction current operation means, so that a decrease in controllability can be suitably avoided.

In a second aspect based on the first aspect , the orthogonal direction current operating means and the magnetic pole direction current operating means set the command voltage of the two-dimensional coordinate system to a fixed value determined based on the input voltage of the power conversion circuit. It is a thing to do.

  According to the above invention, the control amount can be suitably controlled by the phase of the command voltage.

According to a third invention, in the first or second invention, the control amount is a torque of the rotating machine, and the priority means is at least one of a torque command value for the rotating machine and a torque of the rotating machine. To determine whether or not the torque of the rotating machine exceeds a predetermined value.

  In the above invention, since the controlled variable is torque, it is considered that the torque command value approximates the actual torque with high accuracy. For this reason, the determination of whether or not the torque of the rotating machine is equal to or greater than a predetermined value is not limited to the torque of the rotating machine itself, and a torque command value can be used.

According to a fourth invention, in any one of the first to third inventions, the priority unit receives at least one of a current flowing through the rotating machine and a command value of a current for the rotating machine as an input, and the torque of the rotating machine is It is characterized by determining whether it becomes more than predetermined.

  The current flowing through the rotating machine is a parameter having a correlation with the torque of the rotating machine. In the above invention, in view of this point, the above determination is made based on the current.

A fifth invention is characterized in that, in the third or fourth invention, the priority means takes into account the rotational speed of the rotating machine in the determination.

  The relationship between the current in the orthogonal direction component and the torque depends on the rotational speed. For this reason, it is considered that the region where the controllability by the orthogonal current operation means is lowered also depends on the rotation speed. In the above invention, in view of this point, by performing the above determination in consideration of the rotation speed, it is possible to specify with high accuracy a region in which the controllability by the orthogonal current operation means is concerned.

According to a sixth invention, in any one of the first to fifth inventions, the control amount is controlled by feedback control of the control amount to a command value.

According to a seventh invention, in any one of the first to sixth inventions, the priority means selects one of the orthogonal direction current operation means and the magnetic pole direction current operation means according to the torque of the rotating machine. The magnetic pole direction current operating means includes a means for setting a command current of the magnetic pole direction component based on an integral operation according to a difference between the control amount and the command value, and When switching to control by the magnetic pole direction current operating means by the priority means, the initial value of the integral calculation for setting the command current of the magnetic pole direction component is set according to the actual current of the magnetic pole direction component. Features.

  When switching to control by the magnetic pole direction current operating means, it is desirable that the initial value be an appropriate value for smooth switching since the magnetic pole direction current operating means performs integral calculation. However, there is no command current of the magnetic pole direction component in the orthogonal direction current operating means. For this reason, in the said invention, smoothing of switching is aimed at by making the electric current of the present magnetic pole direction component into the initial value of integral calculation.

According to an eighth invention, in any one of the first to seventh inventions, the priority means selects one of the orthogonal direction current operation means and the magnetic pole direction current operation means in accordance with the torque of the rotating machine. The orthogonal direction current operating means includes means for setting a command current of the orthogonal direction component based on an integral calculation according to a difference between the control amount and the command value, and When switching to the control by the orthogonal direction current operation means by the priority means, the initial value of the integration calculation for setting the command current of the orthogonal direction component is set according to the actual current of the orthogonal direction component. Features.

  When switching to the control by the orthogonal direction current operating means, the initial value is preferably set to an appropriate value as long as the orthogonal direction current operating means performs the integral calculation. However, there is no command current of the orthogonal direction component in the magnetic pole direction current operating means. For this reason, in the said invention, smoothing of switching is aimed at by making the electric current of the present orthogonal direction component into the initial value of integral calculation.

According to a ninth invention, in any one of the first to eighth inventions, the priority means selects one of the orthogonal direction current operation means and the magnetic pole direction current operation means in accordance with the torque of the rotating machine. The orthogonal direction current operating means includes means for calculating a command voltage of the magnetic pole direction component based on an integral operation according to a difference between the command current of the orthogonal direction component and an actual current. The magnetic pole direction current operation means includes means for calculating a command voltage of the magnetic pole direction component based on an integral operation according to a difference between the command current of the magnetic pole direction component and an actual current, and the magnetic pole direction component is operated by the priority means. Integral for calculating a command voltage of the magnetic pole direction component for the other when switching from control by one of the directional current operation means and control by the other of the orthogonal current operation means An initial value of the calculation is set based on the one integral calculation value.

  In the above invention, since the magnetic pole direction current operating means and the orthogonal direction current operating means include means for calculating the voltage of the magnetic pole direction component based on the integral calculation, the initial value of the integral calculation is set when switching between these two operating means. An appropriate value is desirable for smooth switching. In this regard, in the above invention, the initial value of the other integral calculation is set based on one of the integral calculation values, thereby facilitating the switching.

According to a tenth aspect of the present invention, in any one of the first to ninth aspects, the low voltage that feedback-controls the current flowing through the rotating machine to the command value in a situation where the voltage utilization rate of the power conversion circuit is not more than a predetermined value A control means, wherein the orthogonal direction current operation means and the magnetic pole direction current operation means are means for operating the power conversion circuit in place of the low voltage control means in a region where the voltage utilization rate is high. And

  It is known that the controllability of the means for feedback-controlling the current flowing through the rotating machine to its command value decreases as the voltage utilization rate increases. In this regard, in the above-described invention, switching to control by the magnetic pole direction current operation means or control by the orthogonal direction current operation means in a region where the voltage utilization factor is high can suitably suppress a decrease in controllability in a region where the voltage utilization factor is high. be able to.

In an eleventh aspect based on the tenth aspect , the low voltage control means includes setting means for setting command values of both the magnetic pole direction component and the orthogonal direction component for the current flowing through the rotating machine, When switching from the control by the magnetic pole direction current operation means to the control by the low voltage control means, the command value of the magnetic pole direction component is changed from the command value of the current of the magnetic pole direction component by the magnetic pole direction current operation means by the setting means. The command value of the orthogonal direction component is gradually shifted to the command value set by the setting means from the actual current of the orthogonal direction component while being gradually shifted to the set command value. .

  At the switching timing from the control by the magnetic pole direction current operation means to the control by the low voltage control means, the command current set by the setting means may be largely separated from the current actually flowing through the rotating machine at that time. . In this case, if the command current set by the setting means is used, the current flowing through the rotating machine may change rapidly, and the controllability of the rotating machine may be reduced. In the above invention, in view of this point, the switching can be smoothly performed by gradually shifting to the command current set by the setting means.

In a twelfth aspect based on the tenth or eleventh aspect , the low voltage control means includes setting means for setting command values for both the magnetic pole direction component and the orthogonal direction component for the current flowing through the rotating machine. And when switching from the control by the orthogonal direction current operation means to the control by the low voltage control means, the command value of the orthogonal direction component is changed from the command value of the current of the orthogonal direction component by the orthogonal direction current operation means. The command value of the magnetic pole direction component is gradually shifted to the command value set by the setting means, and the command value of the magnetic pole direction component is gradually shifted from the actual current of the magnetic pole direction component to the command value set by the setting means. Features.

  At the switching timing from the control by the orthogonal current operation means to the control by the low voltage control means, the command current set by the setting means may be greatly separated from the current actually flowing through the rotating machine at that time. . In this case, if the command current set by the setting means is used, the current flowing through the rotating machine may change rapidly, and the controllability of the rotating machine may be reduced. In the above invention, in view of this point, the switching can be smoothly performed by gradually shifting to the command current set by the setting means.

In a thirteenth aspect based on any one of the tenth to twelfth aspects, the low voltage control means sets command values for both the magnetic pole direction component and the orthogonal direction component for the current flowing through the rotating machine. Setting means, and the magnetic pole direction current operating means includes means for setting a command current of the magnetic pole direction component based on an integral calculation according to a difference between the control amount and a command value thereof, and the low voltage control When switching from the control by means to the control by the magnetic pole direction current operation means, the initial value of the integral calculation for setting the command current of the magnetic pole direction component is set to the command value of the magnetic pole direction component set by the setting means. It is characterized by.

  In the above invention, since the magnetic pole direction current operating means sets the command current of the magnetic pole direction component based on the integral calculation, when switching from the control by the low voltage control means to the control by the magnetic pole direction current operating means, the integral calculation initial stage An appropriate value is desirable for smooth switching. In this respect, in the above invention, the initial value can be appropriately set by using the command value of the magnetic pole direction component set by the setting means.

In a fourteenth aspect based on any one of the tenth to thirteenth aspects, the low voltage control means sets both command values for the magnetic pole direction component and the orthogonal direction component for the current flowing through the rotating machine. Setting means, wherein the orthogonal current operation means includes means for setting a command current of the orthogonal component based on an integral operation according to a difference between the control amount and a command value thereof, and the low voltage control When switching from the control by the means to the control by the orthogonal direction current operation means, the initial value of the integral calculation for setting the instruction current of the orthogonal direction component is set to the command value of the orthogonal direction component set by the setting means. It is characterized by.

  In the above invention, since the orthogonal direction current operating means sets the command current of the orthogonal direction component based on the integral calculation, when switching from the control by the low voltage control means to the control by the orthogonal direction current operating means, the initial value of the integral calculation is set. An appropriate value is desirable for smooth switching. In this regard, in the above invention, the initial value can be appropriately set by using the command value of the orthogonal direction component set by the setting means.

According to a fifteenth aspect , in any one of the tenth to fourteenth aspects, the low voltage control means performs an integral operation according to a difference between a current flowing through the rotating machine and a command value in the two-dimensional coordinate system. The command voltage in the two-dimensional coordinate system is set on the basis of the control voltage, and the command voltage in the two-dimensional coordinate system is changed when switching from the control by the magnetic pole direction current operation means to the control by the low voltage control means. An initial value of the integral calculation for setting is set according to a command voltage of the two-dimensional coordinate system by the magnetic pole direction current operation means.

  In the above invention, since the low voltage control means sets the command voltage based on the integral calculation, when switching from the control by the magnetic pole direction current operation means to the control by the low voltage control means, the initial value of the integral calculation is set. An appropriate value is desirable for smooth switching. In this regard, in the above invention, the initial value can be appropriately set by using the command voltage by the magnetic pole direction current operation means.

According to a sixteenth aspect of the present invention, in any one of the tenth to fifteenth aspects, the low voltage control means is an integral operation according to a difference between a current flowing through the rotating machine and a command value in the two-dimensional coordinate system. The command voltage in the two-dimensional coordinate system is set on the basis of the two-dimensional coordinate system. When switching from the control by the orthogonal current operation means to the control by the low-voltage control means, the command voltage in the two-dimensional coordinate system is An initial value of the integral calculation for setting is set according to a command voltage of the two-dimensional coordinate system by the orthogonal current operation means.

  In the above invention, since the low voltage control means sets the command voltage based on the integral calculation, when switching from the control by the orthogonal current operation means to the control by the low voltage control means, the initial value of the integral calculation is set. An appropriate value is desirable for smooth switching. In this regard, in the above-described invention, the initial value can be appropriately set by using the command voltage by the orthogonal current operation means.

In a seventeenth aspect based on any one of the tenth to sixteenth aspects, the low voltage control means is an operation amount for performing feedback control of the current flowing through the rotating machine in the two-dimensional coordinate system to its command value. The command voltage in the two-dimensional coordinate system is set as follows, and the magnetic pole direction current operating means is configured to perform the magnetic field in the magnetic pole direction based on an integral calculation according to the difference between the command current of the magnetic pole direction component and the actual current. The command voltage is set, and when switching from the control by the low voltage control means to the control by the magnetic pole direction current operation means, the initial value of the integral calculation for setting the command voltage in the magnetic pole direction is It is set based on the command voltage of the magnetic pole direction component by the low voltage control means.

  In the above invention, since the magnetic pole direction current operating means sets the command voltage in the magnetic pole direction based on the integral calculation, when switching from the control by the low voltage control means to the control by the magnetic pole direction current operating means, the initial value of the integral calculation An appropriate value is desirable for smooth switching. In this respect, in the above invention, the initial value can be appropriately set by using the command voltage of the magnetic pole direction component set by the low voltage control means.

In an eighteenth aspect based on any one of the tenth to seventeenth aspects, the low voltage control means is an operation amount for feedback-controlling the current flowing through the rotating machine in the two-dimensional coordinate system to its command value. The command voltage in the two-dimensional coordinate system is set as follows, and the orthogonal direction current operating means is based on the integral calculation according to the difference between the command current of the orthogonal direction component and the actual current. The command voltage is set, and when switching from the control by the low voltage control means to the control by the orthogonal direction current operation means, the initial value of the integral calculation for setting the command voltage in the magnetic pole direction is It is set based on the command voltage of the magnetic pole direction component by the low voltage control means.

  In the above invention, since the orthogonal current operation means sets the command voltage in the magnetic pole direction based on the integral calculation, the initial value of the integral calculation is required when switching from the control by the low voltage control means to the control by the orthogonal current operation means. An appropriate value is desirable for smooth switching. In this respect, in the above invention, the initial value can be appropriately set by using the command voltage of the magnetic pole direction component set by the low voltage control means.

(First embodiment)
Hereinafter, a first embodiment in which a rotating machine control device according to the present invention is applied to a hybrid vehicle control device will be described with reference to the drawings.

  FIG. 1 shows the overall configuration of a motor generator control system according to this embodiment. The motor generator 10 is a three-phase permanent magnet synchronous motor. The motor generator 10 is a rotating machine (saliency pole machine) having saliency. Specifically, the motor generator 10 is an embedded magnet synchronous motor (IPMSM).

  The motor generator 10 is connected to the high voltage battery 12 via the inverter IV. The inverter IV includes a series connection body of the switching elements Sup and Sun, a series connection body of the switching elements Svp and Svn, and a series connection body of the switching elements Swp and Swn. The motor generator 10 is connected to the U, V, and W phases, respectively. In the present embodiment, insulated gate bipolar transistors (IGBTs) are used as the switching elements Sup, Sun, Svp, Svn, Swp, and Swn. In addition, diodes Dup, Dun, Dvp, Dvn, Dwp, and Dwn are connected in antiparallel to these.

  In this embodiment, the following is provided as detection means for detecting the state of the motor generator 10 and the inverter IV. First, current sensors 16, 17 and 18 for detecting currents iu, iv and iw flowing through the respective phases of the motor generator 10 are provided. Furthermore, a voltage sensor 19 for detecting an input voltage (power supply voltage VDC) of the inverter IV is provided.

  The detection values of the various sensors are taken into the control device 14 constituting the low pressure system via the interface 13. The control device 14 generates and outputs an operation signal for operating the inverter IV based on the detection values of these various sensors. Here, the signals for operating the switching elements Sup, Sun, Svp, Svn, Swp, Swn of the inverter IV are the operation signals gup, gun, gvp, gvn, gwp, gwn.

  FIG. 2 shows a block diagram of processing relating to generation of the operation signal of the inverter IV.

In the present embodiment, current vector control and field weakening control are performed. In the following, “processing related to current vector control”, “processing related to field weakening control”, “switching processing between current vector control and field weakening control” will be described in this order, and then “switching processing in field weakening control” will be described.
<Processing related to vector control>
The currents iu, iv, iw flowing through each phase of the motor generator 10 are converted into an actual current iα on the α axis and an actual current iβ on the β axis, which are actual currents in the fixed two-phase coordinate system, in the αβ conversion unit 20. Is done. The real currents iα and iβ are converted by the dq converter 22 into a real current id on the d axis and a real current iq on the q axis, which are real currents in the rotating two-phase coordinate system. The current vector control unit 100 performs current vector control with the actual currents id, iq and the required torque Tr as inputs.

  That is, the command current setting unit 102 sets the command current idr on the d axis and the command current iqr on the q axis, which are command values of the current in the rotating two-phase coordinate system, based on the required torque Tr. The subtraction unit 104 calculates a subtraction value Δid by subtracting the actual current id on the d axis from the command current idr on the d axis. The feedback control unit 106 calculates an operation amount for performing feedback control of the actual current id to the command current idr based on the subtraction value Δid. Specifically, here, proportional-integral calculation is performed. On the other hand, the interference term calculation unit 108 calculates the interference term by multiplying the actual current iq on the q axis by the electrical angular velocity ω and the inductance Lq. The non-interference control unit 110 calculates the command voltage vdr by subtracting the output of the interference term calculation unit 108 from the output of the feedback control unit 106.

  On the other hand, the subtraction unit 112 calculates the subtraction value Δiq by subtracting the actual current iq on the q axis from the command current iqr on the q axis. The feedback control unit 114 calculates an operation amount for performing feedback control of the actual current iq to the command current iqr based on the subtraction value Δiq. Specifically, here, proportional-integral calculation is performed. On the other hand, the interference term calculation unit 116 calculates the interference term by multiplying the actual current id on the d axis by the electrical angular velocity ω and the inductance Ld. The non-interference control unit 118 subtracts the output of the interference term calculation unit 116 from the output of the feedback control unit 114. The induced voltage calculation unit 120 calculates the induced voltage by multiplying the electrical angular velocity ω by a constant Φ. The induced voltage compensator 122 calculates the command voltage vqr by adding the output of the induced voltage calculator 120 to the output of the non-interference controller 118.

The command voltages vdr and vqr are output from the current vector control unit 100 to the three-phase conversion unit 32 via the selector 30. The three-phase conversion unit 32 converts the command voltages vdr, vqr on the dq axis into three-phase command voltages vur, vvr, vwr. The operation signal generator 34 generates command signals by using the command voltages vur, vvr, and vwr as signal waves and comparing the magnitudes of these with the carrier.
<Processing for field weakening control>
In the field weakening control unit 200, the torque estimator 202 estimates the torque of the motor generator 10 based on the actual currents id and iq on the dq axis (calculates the estimated torque Te). On the other hand, the deviation calculating unit 204 calculates a difference between the required torque Tr and the estimated torque Te. The output of the deviation calculation unit 204 is taken into the q-axis current operation unit 210 and the d-axis current operation unit 220.

  Here, in the q-axis current operation unit 210, the torque controller 212 calculates a command current iqr on the q-axis as an operation amount for performing feedback control of the estimated torque Te to the required torque Tr. Specifically, this process is performed by a proportional-integral calculation of the difference between the required torque Tr and the estimated torque Te. On the other hand, the deviation calculation unit 214 calculates the difference between the command current iqr and the actual current iq on the q axis. The current controller 216 sets the command voltage vdr on the d axis as an operation amount for feedback control of the actual current iq on the q axis to the command current iqr. Specifically, the current controller 216 sets the command voltage vdr by integration calculation.

  On the other hand, in the d-axis current operation unit 220, the torque controller 222 calculates a command current idr on the d-axis as an operation amount for performing feedback control of the estimated torque Te to the required torque Tr. Specifically, this process is performed by a proportional-integral calculation of the difference between the required torque Tr and the estimated torque Te. On the other hand, the deviation calculator 224 calculates the difference between the command current idr and the actual current id on the d axis. The current controller 226 sets the command voltage vdr on the d axis as an operation amount for feedback control of the actual current id on the d axis to the command current idr. Specifically, the current controller 226 sets the command voltage vdr by proportional integration calculation.

  By selecting either the command voltage vdr set by the q-axis current operation unit 210 or the command voltage vdr set by the d-axis current operation unit 220 by the selector 230, the command voltage of the field weakening control unit 200 is selected. vdr. On the other hand, the q-axis voltage setting unit 232 sets the q-axis command voltage vqr based on the limit voltage VL determined based on the power supply voltage VDC and the command voltage vdr. Specifically, the square root of the square of the limit voltage minus the square of the command voltage vdr is defined as the q-axis command voltage vqr.

  The command voltage vdr on the d-axis and the command voltage vqr on the q-axis are output to the selector 30.

  Note that the rotation angle θ is appropriately used for each of the above processes. In this embodiment, since a sensorless system is employed, the rotation angle θ estimated based on the electrical state quantity of the motor generator 10 is used. Specifically, in this embodiment, an extended induced voltage observer 40 is provided. The extended induced voltage observer 40 basically performs the processing described in “Extended induced voltage observer for sensorless control of salient pole type brushless DC motor 1999 National Institute of Electrical Engineers of Japan No. 1026”. . That is, based on the actual currents iα and iβ in the fixed two-phase coordinate system and the applied voltage (output of the fixed coordinate conversion unit 42) in the fixed two-phase coordinate system, the angle correlation amount correlated with the rotation angle θ is fixed 2 The extended induced voltage in the phase coordinate system is estimated, and the rotation angle θ is estimated based on this. On the other hand, the speed calculation unit 44 calculates the electrical angular speed ω based on the time differential calculation of the rotation angle θ. Incidentally, the fixed coordinate conversion unit 42 that outputs the applied voltage information to the extended induced voltage observer 40 performs a process of converting the command voltages vdr and vqr into a command voltage on the αβ axis. However, at the time of control by the field weakening control unit 200, the fluctuation range of the command voltages vur, vvr, and vwr output from the three-phase conversion unit 32 exceeds the power supply voltage VDC as will be described later, so that the effective value of the output voltage of the inverter IV is It is desirable to set the command voltage on the αβ axis so as to be equal to the voltages vdr and vqr.

The estimation of the rotation angle θ by the extended induced voltage observer 40 is effective in a region where the electrical angular velocity ω is large. On the other hand, when the control by the current vector control unit 100 is performed, the electrical angular velocity ω of the motor generator 10 can be excessively decreased. For this reason, in the present embodiment, when the current vector control unit 100 performs the control, the rotation angle θ is estimated by another known method in the low rotation speed operation region. Is omitted.
<Switching process between current vector control and field weakening control>
FIG. 3 shows a current vector control region and a field weakening control region according to this embodiment. As shown in the figure, field weakening control is performed in a region where the rotational speed is high. Specifically, field-weakening control is performed at a lower rotational speed as the absolute value of torque is larger.

  FIG. 4 shows a procedure of switching processing from the vector control to the field weakening control according to the present embodiment. This process is repeatedly executed by the control device 14 at a predetermined cycle, for example.

  In this series of processing, first, in step S2, it is determined whether or not a current vector control mode flag, which is a flag indicating that current vector control is being executed, is on. If it is determined that the current vector control mode is set, it is determined in step S4 whether or not the vector norm of the command voltages vdr and vqr is equal to or higher than the limit voltage VL. Here, the limit voltage VL is a value obtained by multiplying the power supply voltage VDC by the square roots of “1.2” and “3/8”. Here, the square root of “3/8” is multiplied by the maximum value of the command voltages vur, vvr, vwr multiplied by the square root of “3/8” to be the norm of the voltage vector on the dq axis. For the reason. Further, “1.2” is set based on the upper limit value that can maintain the controllability of the current vector control. Incidentally, in the present embodiment, the above value is determined in view of the fact that the upper limit value tends to decrease in the sensorless system as compared with the case where the rotation angle is detected by a sensor. For this reason, it is possible to determine whether or not the current vector control can be maintained in step S4. If an affirmative determination is made in step S4, in step S6, the current vector control mode flag is turned off and the field weakening control mode flag is turned on, so that the current vector control is switched to field weakening control.

  When a negative determination is made in steps S2 and S4, or when the process of step S6 is completed, this series of processes is temporarily terminated.

  FIG. 5 shows a procedure of processing relating to switching from field-weakening control to current vector control according to the present embodiment. This process is repeatedly executed by the control device 14 at a predetermined cycle, for example.

  In this series of processes, first, in step S10, it is determined whether or not the field weakening control mode flag is in an ON state. If the field weakening control mode flag is on, the estimated torque Te is calculated based on the actual currents id and iq in step S12. In subsequent step S14, based on the estimated torque Te, command currents idr and iqr for realizing this by current vector control are estimated. This can be estimated and calculated as an output when the estimated torque Te is input to a calculation means that performs the same processing as the command current setting unit 102 shown in FIG.

  In subsequent step S16, based on the estimated command currents idr and iqr, the command voltages vdr1 and vqr1 for realizing this by current vector control are estimated. This can be done using well-known voltage equations.

  In the subsequent step S18, it is determined whether or not the estimated vector norm of the command voltages vdr1 and vqr1 is equal to or less than a value obtained by subtracting a predetermined value Δ from the limit voltage VL. This process determines whether or not the command voltages vur, vvr, and vwr required when the estimated torque Te is generated by current vector control correspond to a value smaller than the modulation factor “1.2”. Is. Here, the predetermined value Δ is a positive number, and switching from current vector control to field weakening control by the process shown in FIG. 4 and switching from field weakening control to current vector control by the process shown in FIG. It is provided to avoid hunting. If an affirmative determination is made in step S18, the current vector control mode flag is turned on and the field weakening field control mode flag is turned off in step S20 to switch to current vector control.

  When a negative determination is made in steps S10 and S18, or when the process of step S20 is completed, this series of processes is temporarily terminated.

  FIG. 6 shows a procedure for setting initial values of current vector control when switching from field weakening control to current vector control. This process is repeatedly executed by the control device 14 at a predetermined cycle, for example.

  In this series of processing, first, in step S30, it is determined whether or not it is time to switch from field weakening control to current vector control. If an affirmative determination is made in step S30, it is determined in step S32 whether or not the control is switched from the control by the q-axis current operation unit 210. If an affirmative determination is made in step S32, initial values of the command currents idr and iqr are set in step S34. Here, in order to avoid a sudden change in the actual currents id and iq, the current on the dq axis controlled by the field weakening control is gradually shifted to the command currents idr and iqr set by the command current setting unit 102. Process.

  That is, the command current idr on the d axis is set as a weighted average value of the current idlpf obtained by filtering the actual current id on the d axis with a low-pass filter and the command current idr set by the command current setting unit 102. Then, among the weighting coefficients in the weighted average, the coefficient K of the current idlpf is gradually decreased with time, and the coefficient “1-K” of the command current idr set by the command current setting unit 102 is gradually increased with time. Further, the command current iqr (v) is set as a weighted average value of the command current iqr (w) set by the q-axis current operation unit 210 and the command current iqr (v) set by the command current setting unit 102. To do. Then, among the weighting coefficients for the weighted average, the coefficient K of the command current iqr (w) set by the q-axis current operation unit 210 is gradually decreased with time, and the command current iqr (v) set by the command current setting unit 102 is set. The coefficient “1-K” is gradually increased with time.

  In the subsequent step S36, the initial value of the integral term of the feedback control units 106 and 114 is set. Here, the initial value of the integral term is set so as to avoid sudden changes in the command voltages vdr and vqr before and after switching. That is, in order to make the command voltage vdr (v) output from the non-interference control unit 110 coincide with the command voltage vdr (w) by the field weakening control, the integral term Ind of the feedback control unit 106 is set to the command voltage vdr (w). It is assumed that “ω · Lq · iqr (w)” is added. Further, in order to match the command voltage vqr (v) output from the induced voltage compensation unit 122 with the command voltage vqr (w) by the field weakening control, the integral term Inq of the feedback control unit 114 is changed from the command voltage vqr (w) to “ It is assumed that “ω · Ld · idlpf + ωΦ” is subtracted.

  On the other hand, when a negative determination is made in step S32, it is determined that it is time to switch from control by the d-axis current operation unit 220, and the process proceeds to step S38. In step S38, initial values of command currents idr and iqr are set. Here, in order to avoid a sudden change in the actual currents id and iq, the current on the dq axis controlled by the field weakening control is gradually shifted to the command currents idr and iqr set by the command current setting unit 102. Process.

  That is, the command current idr (v) is set as a weighted average value of the command current idr (w) set by the d-axis current operation unit 220 and the command current idr (v) set by the command current setting unit 102. To do. Then, among the weighting coefficients for the weighted average, the coefficient K of the command current idr (w) set by the d-axis current operation unit 220 is gradually decreased with time, and the command current idr (v) set by the command current setting unit 102 is set. The coefficient “1-K” is gradually increased with time. In addition, the command current iqr on the q axis is set as a weighted average value of the current iqlpf obtained by filtering the q-axis actual current iq with a low-pass filter and the command current iqr set by the command current setting unit 102. Then, among the weighting coefficients in the weighted average, the coefficient K of the current iqlpf is gradually decreased with time, and the coefficient “1-K” of the command current iqr set by the command current setting unit 102 is gradually increased with time.

  In the subsequent step S40, the initial value of the integral term of the feedback control units 106 and 114 is set. Here, the initial value of the integral term is set so as to avoid sudden changes in the command voltages vdr and vqr before and after switching. That is, in order to make the command voltage vdr (v) output from the non-interference control unit 110 coincide with the command voltage vdr (w) by the field weakening control, the integral term of the feedback control unit 106 is set to the command voltage vdr (w) by “ω. “Lq · iqlpf” is added. Further, in order to make the command voltage vqr (v) output from the induced voltage compensation unit 122 coincide with the command voltage vqr (w) by field weakening control, the integral term of the feedback control unit 114 is changed from the command voltage vqr (w) to “ω・ Ld · idr + ωΦ ”is subtracted.

  If a negative determination is made in step S30, or if the processes in steps S36 and S40 are completed, this series of processes is temporarily terminated.

  FIG. 7 shows the procedure for setting the initial value of field weakening control when switching from current vector control to field weakening control.

  In this series of processing, first, in step S50, it is determined whether or not it is time to switch from current vector control to field weakening control. When an affirmative determination is made in step S50, in step S52, the integral term of the current controller 216 or the current controller 226 is set to the command voltage vdr (v) set by the current vector control unit 100. In a succeeding step S54, it is determined whether or not it is time to switch to the q-axis current operation unit 210. If it is determined that it is time to switch to the q-axis current operation unit 210, in step S56, the initial value of the integral term of the torque controller 212 is set to the command current idr (v) set by the command current setting unit 102. And On the other hand, if a negative determination is made in step S54, the initial value of the integral term of the torque controller 222 is set to the command current iqr (v) set by the command current setting unit 102 in step S58.

When the process of step S50 is completed or when the processes of steps S56 and S58 are completed, this series of processes is temporarily ended.
<Switching process in field weakening control>
As described above, in the present embodiment, the field weakening control unit 200 includes the q-axis current operation unit 210 and the d-axis current operation unit 220. In the present embodiment, the torque controllability is maintained high by switching between the field weakening control by the q-axis current operation unit 210 and the field weakening control by the d-axis current operation unit 220. This is because the field weakening control by the q-axis current operation unit 210 may cause the control to become unstable during powering control, and the powering control and the regeneration are both controlled by the field weakening control by the d-axis current operation unit 220. This is because the control may become unstable. This will be described in detail below.

  FIG. 8A shows a voltage limit ellipse and an isotorque curve. Here, the voltage limit ellipse limits the vector norm of the voltages vd and vq on the dq axis under the condition that the time differential value of the actual currents id and iq is zero in a well-known voltage equation on the dq axis. It is obtained by plotting the actual currents id and iq that become the voltage VL. Incidentally, the voltage limit ellipse depends on the electrical angular velocity ω, but FIG. 8A shows the voltage limit ellipse when the electrical angular velocity ω is a predetermined value. On the other hand, the equal torque curve is a curve obtained by connecting actual currents id and iq that can make the torque a predetermined value. At the time of field weakening control, the estimated torque Te is feedback-controlled to the required torque Tr in such a manner that the vector norm of the command voltages vdr and vqr is set to the limit voltage VL, so that it is on the intersection of the equal torque curve and the voltage limit ellipse. It is considered that the actual currents id and iq are controlled.

  Here, of the intersections of the equal torque curve and the voltage limit ellipse, the relationship between the q-axis current and the torque is shown in FIG. 8B, and the relationship between the d-axis current and the torque is shown in FIG. 8C. Show.

  As shown in FIG. 8B, although the relationship between the q-axis current and the torque has a good linearity, in the region where the torque is large, the change in the torque with respect to the change in the q-axis current becomes large, and the torque is excessively increased. In a region where is large, the torque is not uniquely determined with respect to the q-axis current. From this, it is considered that the field weakening control by the q-axis current operation unit 210 is less controllable in a region where the torque is large. Specifically, in a region where the q-axis current is large, the controllability of torque becomes unstable, and when the torque becomes excessively large, the control may fail.

  On the other hand, as shown in FIG. 8C, the torque change with respect to the d-axis current change is smooth, but the torque is not uniquely determined with respect to the d-axis current. This is because the torque decreases as the d-axis current increases on the power running side, and the torque increases as the d-axis current increases on the regeneration side. Incidentally, the point at which the torque changes from increasing to decreasing with increasing d-axis current is not necessarily the point at which the torque becomes strictly zero, but motor parameters such as the resistance and inductance of the motor generator 10, permanent magnet magnetic flux, It varies depending on the rotation speed and further the limit voltage VL.

  As shown in FIG. 8B and FIG. 8C, although there is a region showing a good linearity between the d-axis current and the q-axis current, the total torque A relationship having good linearity in the region cannot be maintained. For this reason, it is difficult to maintain high controllability in the entire torque region using one of the q-axis current operation unit 210 and the d-axis current operation unit 220.

  Therefore, in the present embodiment, field weakening control by the d-axis current operation unit 220 is performed in a high torque region where the controllability by the q-axis current operation unit 210 decreases. Specifically, field weakening control by the d-axis current operation unit 220 is performed during power running control, and field weakening control by the q-axis current operation unit 210 is performed during regeneration control.

  FIG. 9 shows a procedure of switching processing between the q-axis current operation unit 210 and the d-axis current operation unit 220 according to the present embodiment. This process is repeatedly executed by the control device 14 at a predetermined cycle, for example.

  In this series of processing, first, in step S60, power running and regeneration are determined. In the present embodiment, this determination is made based on the sign of the estimated torque Te. In the subsequent step S62, it is determined whether or not the q-axis current operation mode flag, which is a flag indicating that field weakening control by the q-axis current operation unit 210 is performed, is on. If an affirmative determination is made in step S62, it is determined in step S64 whether or not it is during power running control. This process is for determining whether or not to switch to field weakening control by the d-axis current operation unit 220. If an affirmative determination is made in step S64, in step S66, the d-axis current operation mode flag, which is a flag for performing field weakening control by the d-axis current operation unit 220, is turned on, and the q-axis current operation mode flag is turned off. In the subsequent step S68, an initial value of the d-axis current operation unit 220 is set. That is, the initial value of the integrator of the torque controller 222 is the current idlpf obtained by processing the d-axis actual current id with a low-pass filter. The initial value of the integrator of the current controller 226 is set as the command voltage vdr of the q-axis current operation unit 210.

  On the other hand, if a negative determination is made in step S62, it is determined in step S70 whether or not the d-axis current operation mode flag is on. If an affirmative determination is made in step S70, it is determined in step S72 whether or not it is during regenerative control. This process is for determining whether it is time to switch to field weakening control by the q-axis current operation unit 210. If it is determined that the regeneration control is being performed, in step S74, the d-axis current operation mode flag is turned off and the q-axis current operation mode flag is turned on. In a succeeding step S76, an initial value of the q-axis current operation unit 210 is set. That is, the initial value of the integrator of the torque controller 212 is a current iqlpf obtained by processing the q-axis actual current iq with a low-pass filter. Further, the initial value of the integrator of the current controller 216 is set as the command voltage vdr of the d-axis current operation unit 220.

  When a negative determination is made in steps S64, S70, and S72, or when the processes in steps S68 and S76 are completed, the series of processes is temporarily terminated.

  FIG. 10A shows the effect of this embodiment. In FIG. 10A, a change in the required torque Tr is indicated by a one-dot chain line, and a change in the estimated torque Te is indicated by a solid line. As shown in the figure, when the required torque Tr is shifted from negative to positive, the estimated torque Te can be made to follow the required torque Tr satisfactorily when shifting from regenerative control to power running control. On the other hand, FIG. 10B shows a case where only field weakening control by the q-axis current operation unit 210 is performed. In this case, the estimated torque Te greatly fluctuates in the high torque region, and the controllability of the torque decreases.

  According to the embodiment described in detail above, the following effects can be obtained.

  (1) When the torque of the motor generator 10 exceeds a predetermined value, the control by the d-axis current operation unit 220 is prioritized over the control by the q-axis current operation unit 210. Thereby, the fall of controllability can be avoided suitably.

  (2) By using the estimated torque Te, it is possible to determine whether or not the torque exceeds a predetermined value without providing a torque sensor.

  (3) When switching from the control by the q-axis current operation unit 210 to the control by the d-axis current operation unit 220, the initial value of the integrator of the torque controller 222 was set according to the actual current id of the d-axis. Thereby, switching can be performed smoothly.

  (4) When switching from the control by the d-axis current operation unit 220 to the control by the q-axis current operation unit 210, the initial value of the torque controller 212 was set according to the q-axis actual current iq. Thereby, switching can be performed smoothly.

  (5) When switching from the control by one of the d-axis current operation unit 220 and the q-axis current operation unit 210 to the control by the other, the initial value of the integration calculation of the other current controller is set to the integration of the one current controller. It was set based on the calculated value. Thereby, switching can be performed smoothly.

  (6) The control by the current vector control unit 100 is switched to the control by the field weakening control unit 200 in a region where the voltage utilization factor is high. Thereby, the fall of controllability in the area | region with a high voltage utilization factor can be suppressed suitably.

  (7) When switching from the control by the d-axis current operation unit 220 to the control by the current vector control unit 100, the d-axis command current idr is changed from the command current idr (w) by the d-axis current operation unit 220. The command current idr (v) set by 102 is gradually shifted, and the q-axis command current iqr is changed from the actual current iq (iqlpf) on the q-axis to the command current iqr ( Gradually shifted to v). Thereby, switching can be performed smoothly.

  (8) When the control by the q-axis current operation unit 210 is switched to the control by the current vector control unit 100, the command current iqr for the q-axis is changed from the command current iqr (w) by the q-axis current operation unit 210 to the command current setting unit. The d-axis command current idr is gradually changed to the command current idr (v) set by the command current setting unit 102 from the d-axis actual current id (idlpf). It was gradually shifted. Thereby, switching can be performed smoothly.

  (9) When switching from the control by the current vector control unit 100 to the control by the d-axis current operation unit 220, the initial value of the integral calculation of the torque controller 222 is set to the command current idr set by the command current setting unit 102 . Thereby, an initial value can be set appropriately.

  (10) When switching from the control by the current vector control unit 100 to the control by the q-axis current operation unit 210, the initial value of the integral calculation of the torque controller 212 is set to the command current iqr set by the command current setting unit 102 . Thereby, an initial value can be set appropriately.

  (11) When switching from the control by the d-axis current operation unit 220 to the control by the current vector control unit 100, the initial value of the integral calculation of the current feedback control units 106 and 114 is set to the command voltages vdr and vqr by the field weakening control unit 200. Set according to. Thereby, an initial value can be set appropriately.

  (12) When switching from the control by the q-axis current operation unit 210 to the control by the current vector control unit 100, the initial value of the integral calculation of the current feedback control units 106 and 114 is set to the command voltages vdr and vqr by the field weakening control unit 200. Set according to. Thereby, an initial value can be set appropriately.

  (13) When switching from the control by the current vector control unit 100 to the control by the d-axis current operation unit 220, the initial value of the integrator of the current controller 226 is set as the command voltage vdr of the current vector control unit 100. Thereby, an initial value can be set appropriately.

  (14) When switching from the control by the current vector control unit 100 to the control by the q-axis current operation unit 210, the initial value of the integrator of the current controller 216 is set as the command voltage vdr of the current vector control unit 100. Thereby, an initial value can be set appropriately.

(Second Embodiment)
Hereinafter, the second embodiment will be described with reference to the drawings with a focus on differences from the first embodiment.

  In the present embodiment, under the situation where the field weakening control unit 200 performs the control, the contribution ratio between the control by the q-axis current operation unit 210 and the control by the d-axis current operation unit 220 is variably set stepwise or continuously. When the torque exceeds a predetermined value, the control by the d-axis current operation unit 220 is prioritized.

  FIG. 11 shows a block diagram of processing related to generation of an operation signal of the inverter IV according to the present embodiment. In FIG. 11, processes corresponding to the processes shown in FIG. 2 are given the same reference numerals for convenience.

  As illustrated, the multiplication unit 240 multiplies the output of the q-axis current operation unit 210 by a weighting factor α. In addition, the multiplication unit 242 multiplies the output of the d-axis current operation unit 220 by a weighting factor β. These weight coefficients α and β have a relationship of “α + β = 1”. For this reason, the adding unit 244 can calculate the weighted average value of the output of the q-axis current operation unit 210 and the output of the d-axis current operation unit 220 by adding the outputs of the multiplication units 240 and 242. The value calculated in this way is the command voltage vdr. Here, in the present embodiment, the weight coefficients α and β are variably set according to the estimated torque Te. In particular, the larger the estimated torque Te is, the larger the weight coefficient β is. When the torque is greater than or equal to a predetermined value, the weight coefficient β is larger than the weight coefficient α.

  Also according to the present embodiment described above, the effects (1) and (2) of the first embodiment can be obtained.

(Other embodiments)
Each of the above embodiments may be modified as follows.

  In the first embodiment, torque control by the q-axis current operation unit 210 and torque control by the d-axis current operation unit 220 are switched based on the estimated torque Te. However, the present invention is not limited to this. For example, switching may be performed based on the required torque Tr. For example, if a sensor for detecting the torque of the motor generator 10 is provided, the detection may be performed based on the detected value of the torque. Furthermore, for example, switching may be performed based on the actual current iq, or switching may be performed based on the command current iqr. Furthermore, the parameter relating to the current used for switching is not limited to the current on the dq axis, but may be a phase current. Further, instead of switching based on either torque or current, switching may be performed based on both. Furthermore, you may consider a rotational speed.

  In the second embodiment, the priority between the torque control by the q-axis current operation unit 210 and the torque control by the d-axis current operation unit 220 is variably set stepwise or continuously based on the estimated torque Te. Not limited to this. For example, it may be variably set based on the required torque Tr. Further, for example, if a sensor for detecting the torque of the motor generator 10 is provided, it may be variably set based on the detected value of the torque. Further, for example, the variable setting may be performed based on the actual current iq, or the variable setting may be performed based on the command current iqr. Furthermore, the parameter relating to the current used for variable setting is not limited to the current on the dq axis, but may be a phase current. Further, instead of performing variable setting based on either torque or current, variable setting may be performed based on both. Furthermore, you may consider a rotational speed.

  The torque controller 212 in the q-axis current operation unit 210 is not limited to a proportional integral controller. For example, a proportional controller, an integral controller, a proportional integral derivative controller, or the like may be used.

  The current controller 216 in the q-axis current operation unit 210 is not limited to an integral controller. For example, a proportional integral controller or a proportional integral derivative controller may be used.

  The q-axis current operation unit 210 is not limited to those illustrated in the above embodiments and their modifications, and may be, for example, the means described in Non-Patent Document 1 above.

  The torque controller 222 in the d-axis current operation unit 220 is not limited to a proportional integral controller. For example, a proportional controller, an integral controller, a proportional integral derivative controller, or the like may be used.

  The current controller 226 in the d-axis current operation unit 220 is not limited to a proportional integral controller. For example, a proportional controller, an integral controller, a proportional integral derivative controller, or the like may be used.

  The configuration of the current vector control unit 100 is not limited to that illustrated in the above embodiments. For example, the feedback control units 106 and 114 may be configured by a proportional integral derivative controller instead of the proportional integral controller. Further, the feedback control units 106 and 114 may be provided with only a proportional controller and a means for calculating a feedforward voltage corresponding to the command currents idr and iqr. Further, only the feedback control units 106 and 114 may be provided without providing compensation terms and interference terms related to the induced voltage as feedforward terms.

  The means for acquiring information about the actual torque is not limited to the torque estimator 202, and may be a means for acquiring the detected value if the apparatus includes a torque sensor.

  In each of the above embodiments, the command voltage vdr set by the field weakening control unit 200 is set as the final operation amount for torque feedback control, but is not limited thereto. For example, as in Non-Patent Document 1, means for setting the command voltage vdr as an open loop operation amount for controlling the required torque Tr may be used.

  The control amount of the motor generator 10 is not limited to torque, and may be, for example, a rotational speed.

  The conditions for switching from torque control by the field weakening control unit 200 to control by the current vector control unit 100 are not limited to those exemplified in the above embodiments. For example, as a switching condition from torque control by the d-axis current operation unit 220 to control by the current vector control unit 100, a condition that the command current idr by the d-axis current operation unit 220 is zero or more may be used.

  In each of the above embodiments, the actual current id is filtered by a low-pass filter as an initial value of the d-axis command current idr when switching from torque control by the q-axis current operation unit 210 to control by the current vector control unit 100 However, the present invention is not limited to this. For example, the actual current id itself may be used.

  In each of the above embodiments, the actual current iq is filtered by a low-pass filter as the initial value of the q-axis command current iqr when switching from torque control by the d-axis current operation unit 220 to control by the current vector control unit 100 However, the present invention is not limited to this. For example, the actual current iq itself may be used.

  When the control by the d-axis current operation unit 220 is switched to the control by the current vector control unit 100, the command current idr (v) is changed from the command current idr (w) by the d-axis current operation unit 220 by the command current setting unit 102. A method of gradually shifting to the set command current idr (v) and gradually shifting the command current iqr (v) from the actual current iq (iqlpf) to the command current iqr set by the command current setting unit 102 Is not limited to that exemplified in the first embodiment. For example, the difference between the output of the proportional-plus-integral calculator having the d-axis command current idr (w) by the d-axis current operation unit 220 as an initial value and the command current idr (v) set by the command current setting unit 102 is the above-described value. The input of the proportional integration calculator may be used, and the output of the proportional integration calculator may be adopted as the command current idr while the difference between the output of the proportional integration calculator and the set command current idr (v) is greater than or equal to a predetermined value.

  The command current iqr is set by the command current setting unit 102 from the command current iqr (w) by the q-axis current operation unit 210 when switching from the control by the q-axis current operation unit 210 to the control by the current vector control unit 100. Method of gradually shifting to command current iqr (v) and gradually shifting command current idr (v) from actual current id (idlpf) to command current idr (v) set by command current setting unit 102 Is not limited to that exemplified in the first embodiment. For example, the difference between the output of the proportional-plus-integral calculator having the q-axis command current iqr (w) by the q-axis current operation unit 210 as an initial value and the command current iqr (v) set by the command current setting unit 102 is proportional to the above. The output of the proportional integration calculator may be used as the command current idr while the difference between the output of the proportional integration calculator and the command current iqr (v) is greater than or equal to a predetermined value.

  In each of the above embodiments, when switching from the control by the current vector control unit 100 to the control by the field weakening control unit 200, the initial values of the integrators of the torque controllers 212 and 222 are set as the command current set by the command current setting unit 102. Although iqr and idr are used, the present invention is not limited to this. For example, the actual currents iq and id may be used.

  In each of the above embodiments, the rotation angle θ is estimated using the extended induced voltage observer that receives the actual currents iα and iβ and the applied voltage in the fixed coordinate system, but the present invention is not limited to this. For example, the rotation angle θ may be estimated using an extended induced voltage observer that receives the actual currents id, iq and the applied voltage in the rotating coordinate system.

  The means for acquiring information related to the rotation angle θ is not limited to acquiring the rotation angle θ estimated based on the expansion induced voltage. For example, in a system including a resolver, a means for acquiring the detected value may be used. In this case, the controllability of the control by the current vector control unit 100 tends to be stable up to a voltage utilization rate as compared to the case of sensorless, and in this case, the limit voltage VL is set higher than that in each of the above embodiments. You may set large. However, the value of the limit voltage VL may be appropriately changed according to the required specifications, for example, a value corresponding to the modulation factor “1”.

  In each of the above embodiments, the inverter IV is directly operated with the command voltages vdr and vqr based on the limit voltage VL during the control by the field weakening control unit 200, but the present invention is not limited to this. For example, in a situation where the amplitude center of the phase current varies, an operation amount for controlling this variation may be a correction amount of the vector norm of the command voltages vdr and vqr in the field weakening control unit 200. Even in this case, the relationship between the command current and the torque is considered to approximate the relationship shown in FIGS. 8B and 8C, so that the application of the present invention is effective.

  -The salient pole machine is not limited to IPMSM. For example, a synchronous reluctance motor (SynRM) may be used.

  -A rotary machine is not restricted to what is mounted in a hybrid vehicle, For example, you may mount in an electric vehicle. Furthermore, the rotating machine is not limited to one constituting a vehicle drive system.

1 is a system configuration diagram according to a first embodiment. FIG. The block diagram regarding the production | generation process of the operation signal concerning the embodiment. The figure which shows the switching aspect of the current vector control concerning the same embodiment, and field-weakening control. The flowchart which shows the procedure of the switching process from the current vector control to the field weakening control concerning the embodiment. The flowchart which shows the procedure of the switching process from the field-weakening control to the current vector control concerning the embodiment. The flowchart which shows the procedure of the setting process of the initial value of current vector control at the time of switching from field weakening control to current vector control concerning the embodiment. The flowchart which shows the procedure of the setting process of the initial value of the field weakening control at the time of the switch from the current vector control to the field weakening control concerning the embodiment. The figure explaining the necessity of switching with the q-axis current operation part and d-axis current operation part concerning the embodiment. The flowchart which shows the procedure of the switching process of the q-axis current operation part and d-axis current operation part concerning the embodiment. The time chart which shows the effect of the embodiment. The block diagram regarding the production | generation process of the operation signal concerning 2nd Embodiment.

Explanation of symbols

  DESCRIPTION OF SYMBOLS 10 ... Motor generator, 14 ... Control apparatus, 100 ... Current vector control part (one embodiment of a low voltage control means), 102 ... Command current setting part, 200 ... Field weakening control part, 210 ... q-axis current operation part, 220 ... d-axis current operation unit.

Claims (12)

In a control device for a rotating machine that controls a control amount of the rotating machine by operating a power conversion circuit including a switching element that connects a terminal of the rotating machine to each of a positive electrode and a negative electrode of a DC power supply,
By setting the command voltage of the two-dimensional coordinate system based on the command current of the orthogonal component with respect to the magnetic pole direction of the rotating machine and the input voltage of the power conversion circuit, the control amount is based only on the command current of the orthogonal component. Orthogonal current operation means for controlling
The control amount is controlled based only on the command current of the magnetic pole direction component by setting the command voltage of the two-dimensional coordinate system based on the command current of the magnetic pole direction component of the rotating machine and the input voltage of the power conversion circuit. Magnetic pole direction current operating means,
When the torque of the rotating machine is equal to or greater than a predetermined value, priority means for giving priority to control by the magnetic pole direction current operation means over control by the orthogonal direction current operation means ;
Under the condition that the voltage utilization rate of the power conversion circuit is equal to or less than a predetermined value, low voltage control means for feedback-controlling the current flowing through the rotating machine to its command value,
The orthogonal direction current operating means and the magnetic pole direction current operating means are means for operating the power conversion circuit instead of the low voltage control means in a region where the voltage utilization rate is high . Control device. The priority means selectively uses one of the orthogonal direction current operation means and the magnetic pole direction current operation means according to the torque of the rotating machine,
The magnetic pole direction current operating means includes means for setting a command current of the magnetic pole direction component based on an integral calculation according to a difference between the control amount and its command value, and the magnetic pole direction current operating means by the priority means. when switched to the control by, wherein the initial value of the integral operation for setting the command current of the magnetic pole direction component, in claim 1, characterized in that set in accordance with the actual current of the magnetic pole direction component Rotating machine control device. The priority means selectively uses one of the orthogonal direction current operation means and the magnetic pole direction current operation means according to the torque of the rotating machine,
The orthogonal direction current operation means includes means for setting a command current of the orthogonal direction component based on an integral calculation according to a difference between the control amount and a command value thereof, and the orthogonal direction current operation means by the priority means. The initial value of the integral calculation for setting the command current of the orthogonal direction component is set in accordance with the actual current of the orthogonal direction component when switching to the control according to claim 1 or 2. The control apparatus of the rotary machine as described in 2. The priority means selectively uses one of the orthogonal direction current operation means and the magnetic pole direction current operation means according to the torque of the rotating machine,
The orthogonal direction current operation means includes means for calculating a command voltage of the magnetic pole direction component based on an integral calculation according to a difference between the command current of the orthogonal direction component and an actual current,
The magnetic pole direction current operating means includes means for calculating a command voltage of the magnetic pole direction component based on an integral operation according to a difference between the command current of the magnetic pole direction component and an actual current,
When the priority unit switches from the control by one of the magnetic pole direction current operation unit and the orthogonal direction current operation unit to the control by the other, the integral calculation for calculating the command voltage of the magnetic pole direction component for the other is performed. The control device for a rotating machine according to any one of claims 1 to 3 , wherein an initial value is set based on the one integral calculation value. The low voltage control means includes setting means for setting command values of both the magnetic pole direction component and the orthogonal direction component for the current flowing through the rotating machine,
When switching from the control by the magnetic pole direction current operation means to the control by the low voltage control means, the command value of the magnetic pole direction component is changed from the command value of the current of the magnetic pole direction component by the magnetic pole direction current operation means to the setting means. The command value of the orthogonal direction component is gradually shifted from the actual current of the orthogonal direction component to the command value set by the setting means. The control device for a rotating machine according to any one of claims 1 to 4 . The low voltage control means includes setting means for setting command values of both the magnetic pole direction component and the orthogonal direction component for the current flowing through the rotating machine,
When switching from the control by the orthogonal current operation means to the control by the low voltage control means, the command value of the orthogonal direction component is changed from the command value of the current of the orthogonal direction component by the orthogonal direction current operation means to the setting means. The command value of the magnetic pole direction component is gradually shifted from the actual current of the magnetic pole direction component to the command value set by the setting means. The control device for a rotating machine according to any one of claims 1 to 5 . The low voltage control means includes setting means for setting command values of both the magnetic pole direction component and the orthogonal direction component for the current flowing through the rotating machine,
The magnetic pole direction current operation means includes means for setting a command current of the magnetic pole direction component based on an integral calculation according to a difference between the control amount and its command value, and from the control by the low voltage control means When switching to the control by the magnetic pole direction current operating means, the initial value of the integral calculation for setting the command current of the magnetic pole direction component is set as the command value of the magnetic pole direction component set by the setting means. The control device for a rotating machine according to any one of claims 1 to 6 . The low voltage control means includes setting means for setting command values of both the magnetic pole direction component and the orthogonal direction component for the current flowing through the rotating machine,
The orthogonal direction current operation means includes means for setting a command current of the orthogonal direction component based on an integral calculation according to a difference between the control amount and the command value, and from the control by the low voltage control means. When switching to control by the orthogonal direction current operating means, the initial value of the integral calculation for setting the instruction current of the orthogonal direction component is set as the instruction value of the orthogonal direction component set by the setting means. The control device for a rotating machine according to any one of claims 1 to 7 . The low voltage control means sets a command voltage in the two-dimensional coordinate system based on an integral operation according to a difference between a current flowing through the rotating machine in the two-dimensional coordinate system and a command value thereof,
When switching from the control by the magnetic pole direction current operating means to the control by the low voltage control means, the initial value of the integral calculation for setting the command voltage in the two-dimensional coordinate system is set by the magnetic pole direction current operating means. The control device for a rotating machine according to any one of claims 1 to 8 , wherein the control device is set according to a command voltage of the two-dimensional coordinate system. The low voltage control means sets a command voltage in the two-dimensional coordinate system based on an integral operation according to a difference between a current flowing through the rotating machine in the two-dimensional coordinate system and a command value thereof,
When switching from the control by the orthogonal current operation means to the control by the low voltage control means, the initial value of the integral operation for setting the command voltage in the two-dimensional coordinate system is determined by the orthogonal current operation means. The control device for a rotating machine according to any one of claims 1 to 9 , wherein the control device is set according to a command voltage of the two-dimensional coordinate system. The low voltage control means sets a command voltage in the two-dimensional coordinate system as an operation amount for feedback-controlling the current flowing through the rotating machine in the two-dimensional coordinate system to the command value,
The magnetic pole direction current operation means sets the command voltage in the magnetic pole direction based on an integral calculation according to the difference between the command current of the magnetic pole direction component and the actual current. From the control by the low voltage control means When switching to the control by the magnetic pole direction current operating means, the initial value of the integral calculation for setting the command voltage in the magnetic pole direction is set based on the command voltage of the magnetic pole direction component by the low voltage control means. The control device for a rotating machine according to any one of claims 1 to 10 , wherein: The low voltage control means sets a command voltage in the two-dimensional coordinate system as an operation amount for feedback-controlling the current flowing through the rotating machine in the two-dimensional coordinate system to the command value,
The orthogonal direction current operation means sets the command voltage in the magnetic pole direction based on an integral calculation according to a difference between the instruction current of the orthogonal direction component and an actual current, and is controlled by the low voltage control means. When switching to the control by the orthogonal current operation means, an initial value of the integral calculation for setting the command voltage in the magnetic pole direction is set based on the command voltage of the magnetic pole direction component by the low voltage control means. The control device for a rotating machine according to any one of claims 1 to 11 , wherein:

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