JP4874493B2 - Magnetic control current or voltage regulator and transformer - Google Patents

Abstract

The invention relates to a magnetically influenced current or voltage regulator comprising a body (1) which is composed of a magnetisable material and provides a closed, magnetic circuit, at least one first electrical conductor (8) wound about the body of a first main winding (2) and at least one second electrical conductor (9) wound about the body of a second main winding (4). The winding axis (A2) for the main winding (2) is at right angles to the winding axis (A4) for the control winding (4) with the object of providing orthogonal magnetic fields (H1, B1 and H2, B2 respectively) in the body (1) and thereby controlling the behaviour of the magnetisable material relative to the field (H1, B1) in the main winding (2) by means of the field (H2, B2) in the control winding (4).

Description

Ｅ＝印加電圧
ω＝角周波数
Ｎ＝巻数
ここに、磁気材料を通る磁束Φは電圧Ｅによって決定される。必要な磁束を確立するために必要な電流は次式によって決定される：
２）電流：

３）磁気抵抗（磁束抵抗）

１Ｊ＝磁路長
μｒ＝比透磁率
μ０＝真空中の透磁率
Ａｊ＝磁路の断面積
【００５２】
ここに低磁気抵抗（鉄容器）があると、上式２）により、小さい電流が必要とする磁束を確立するのに必要となり、また印加電圧はコネクタをオーバーレイする。他方、高い磁気抵抗（空気）の場合において、大きい電流が、必要とする磁束を確立するために必要となる。従って、この場合において、電流は負荷にかかる電圧とコネクタ内に誘起される電圧によって制限される。空気中の磁気抵抗と磁気材料中の磁気抵抗間の差は１．０００〜９００．０００台となろう。
【００５３】
磁気材料中の磁気誘導ないし磁束は材料の比透磁率と磁束密度によって決定される。磁界強度は材料の回りまたはその中に配備された巻線内の電流によって発生される。
【００５４】
評価されるべきシステムに対して、次式が適用される：
磁界強度

Ｈ￣＝磁界強度
ｓ＝積分パス（道）
Ｉ＝巻線中の電流
Ｎ＝巻数
磁束密度ないし誘導

Ｈ￣＝磁界強度
【００５５】
磁気誘導と磁界強度間の比は非直線であり、この結果、磁界強度がある一定限度以上に増大すると、強磁性材料の磁気ドメインが飽和状態にあるという事実のために飽和現象の理由で磁束密度は増加しなくなる。従って、磁化材料中の飽和を制御するために磁気材料中の作用磁界Ｈ１と垂直に制御磁界Ｈ２を提供し、他方で二つの磁界間の磁気結合を阻止し、これによって変圧器結合ないし誘導接合を阻止することが望ましい。変圧器結合とは、二つの巻線が磁界を「共有」しており、この結果一つの巻線からの磁界中の変化が他の巻線中の磁界中の変化をもたらすことを意味する。
【００５６】
増大するＨが変圧器結合による飽和を阻止するには、磁束は共通径路を有し、互いに付加されることになる。磁束が直交していれば、磁束は互いに付加されることはない。例えば、磁気材料を管状に提供することにより、主巻線または作用電流の流れている巻線が内部に配備され、管の長手方向に巻回され、制御巻線ないし制御電流の流れている巻線を管の回りに巻回することにより、所望の効果が達成される。管の寸法に依存して、制御磁束のための小さい面積と作用磁束のための大きい面積がこれによって達成される。
【００５７】
前記実施例において、作用磁束は管の円周に沿って流れ、また閉磁気回路ができる。他方において、制御磁束が管の長手方向に流れ、二つの管が並列に配備され、かつ、磁気材料が二つの管間で制御磁束を連結することにより、または第１管が第２管の回りに配置されることにより、閉磁気回路内で結合されることになり、この結果制御巻線が二つの管間に配置され、また管の端面が磁気的に相互連結され、従って、制御磁束のための閉径路が得られる。これらの解決策は後ほどより詳しく説明する。
【００５８】
管間またはコア間の磁気結合を提供する部材は、以後磁気コネクタまたは磁界カップリングと記述する。
【００５９】
材料中の総磁束は、

によって与えられる。
【００６０】
磁束密度ＢはＢ１とＢ２のベクトル和からなる（図４ｄ）．Ｂ１は第１主巻線２中の電流Ｉ１によって発生され、またＢ１は主巻線２内の電導体に対する接線方向を有する。主巻線２はＮ１巻数を有し、かつ、磁化可能本体１の回りに巻回されている。Ｂ２はＮ２巻数の制御巻線４内の電流Ｉ２によって発生され、制御巻線４は本体１の回りに巻回されている。Ｂ２は制御巻線４内の電導体に対して接線方向である。
【００６１】
巻線２と４が互いに９０°で配置されているので、Ｂ１とＢ２は直角に配置されることになる。磁化可能本体１内において、Ｂ１は横切るように、またＢ２は縦方向に向けられる。この点に関しては特に図１〜４に示す。
【００６２】

比透磁率が制御磁界（Ｈ２）方向内よりも作用磁界（Ｈ１）内の方が高い、すなわち、磁化可能本体１内の磁気材料が異方性であるが、もちろん、これは本発明の概念に関して制限することを考慮したものではない。
【００６３】
磁界Ｈ１とＨ２のベクトル和は本体１内の総磁界を決定することになり、また従って、飽和に関する本体１の条件は磁化電流と電圧を決定することになり、これは巻線２に接続された負荷とコネクタ間に分割される。Ｂ１とＢ２の磁束源は互いに直交して配備されているので、どちらの磁界も他方の磁界に分解できない。これはＢ１がＢ２の関数とはならず、またＢ２がＢ１の関数にならないことを意味している。しかし、Ｂ１とＢ２のベクトル和であるＢは両者の各々の範囲によって影響される。
【００６４】
Ｂ２は制御電流によって発生されるベクトルである。Ｂ２ベクトルのための断面Ａ２は磁気本体１の横断面となる。図４ｃ参照。これは磁化可能本体１の厚みによって限定された小さい面となり、環状本体の場合、本体１の内径および外径間の面セクターによって与えられる。一方、Ｂ１磁界のための断面Ａ１（図４ａ，ｂ参照）は磁気コアの長さと印加電圧の定格によって与えられる。この面は制御磁束密度Ｂ２の面よりも５〜１０倍大きくなるが、これは本発明を限定することを考慮するのもではない。
【００６５】
Ｂ２が飽和レベルにあるとき、Ｂ１内の変化はＢ内の変化とならない。これはＢ１が材料の飽和させるレベルを制御することを可能にする。
【００６６】
制御巻線４（Ｎ２巻数のある）のインダクタンスは調整器のパルス制御に適した小さい値に定格付けることができ、すなわち、（ミリ秒台の）高速反応を提供することが可能である。
【００６７】

Ｎ２＝制御巻線の巻数
Ａ２＝制御磁束密度Ｂ２の面積
ｌ２＝制御磁束の磁束路の長さ
【００６８】
簡略化数学的表現を、マックスウエルの方程式に基づいて本発明とその適用例のために次に示す。
【００６９】
電力技術における磁界の簡単な計算のために、マックスウエルの方程式は積分形態で使用される。
【００７０】
ここで分析されることになるタイプの装置（本発明にもある程度の拡張がある）において、磁界は低周波数を有する。
【００７１】
従って、変位電流は電流密度と比較して無視することができる。
【００７２】
マックスウエルの方程式

は

に簡略化される。
【００７３】
積分形態はトーク（Ｔｏｋｅ’ｓ）定理に見つけられる：

は図４内のシステムのための解を表わし、ここに主巻線２がＨ１磁界を確立する。ここでは原理に焦点を絞り、計算は集中巻きの場合で行っておき、正確な計算はしない。
【００７４】
積分パスが磁界方向に一致し、平均磁路長１１は磁化可能本体１内に選択される。積分方程式の解は、

となる。これも起磁力ＭＭＫとして知られている。

【００７５】
制御巻線４は電流Ｉ２によって発生されるＭＭＫに対応して確立する：

【００７６】
ソース巻線２と４から発生されたＨ磁界の影響下にある材料の磁化は磁束密度Ｂで表わされる。主巻線２に対しては：

制御巻線４に対しては：

【００７７】
横方向の透磁率は縦方向よりも１０倍から２０倍程度小さい。真空における透磁率は：

【００７８】
鉄内の磁界を導通する容量は、μ_ｒで与えられ、さらにμの大きさは鉄については１０００から１００．０００であり、また新しいメットグラス（Ｍｅｔｇｌａｓ）材料については最大で９００．０００である。
【００７９】
式１１）と１５）を組み合わせることにより、主巻線２に対して、次式が得られる：

【００８０】
主巻線２からの磁化可能本体１内の磁束は、次式によって与えられる：

【００８１】
磁束がコア断面にわたり一定であると仮定すると：

【００８２】
ここで、３）の下で与えられた磁束抵抗Ｒｍまたは磁気抵抗対する式を確認すると：

【００８３】
同様にして、制御巻線４に対する磁束と磁気抵抗を調べると：

【００８４】
本発明は電導体内の電流中にそのソースを有する磁界強度の差動がＨ磁界に対するベクトル回転によって表現される物理的事実に基づいている。Ｈをベクトル回転するとは、Ｈの磁界方向を横切るＨ磁界の差動ないし磁界変化に関して何かを言うことである。この場合において、差動磁界ループと垂直をなす面が電流と同じ方向を有することに基づいて磁界を計算する。これは互いに垂直をなしている巻線を形成している電流流通電導体からの磁界も直交していることを意味している。互いに垂直である磁界は材料中のドメインの方向性に関して重要であることは事実である。
【００８５】
この点をより綿密に調べる前に、新たな磁気制御電力要素の適用に主要な役割を果たす自己インダクタンスを導入する。
【００８６】
マックスウエルの方程式によれば、経時変化磁界が経時電界を誘導し、

によって表わされる。
【００８７】
積分の左側は積分形態にある電位式を表している。磁界変化の源は発電機からの電圧であり、また、巻線がＮ巻数を有するとき、ファラデーの法則で表わすことができ、また磁束が全ての巻数を通過する。図５参照。

λ（Ｗｂ）は磁束の巻数を表わし、また巻線内の各巻数を通る磁束の和である。磁界が確立された後で、断続された図５ｂ中の発電機Ｇを考察すると、磁束源の変化は回路内の電流であり、また既存の回路技術からきている。図５ａ参照。

【００８８】
式２１から、

が得られる。
【００８９】
Ｌが一定のとき、式２６と式２７の組み合わせにより：

が得られる。
【００９０】
式２９の解は：

である。
【００９１】
式２８から、Ｃが０であることを導き、そして：

を導出する。
【００９２】
これは巻線Ｎ（またはこの場合においては主巻線２）のために自己誘導を表している。自己誘導は巻線（コイル）内の電流によって確立された磁束巻数と巻線（コイル）内の電流間の比に等しい。
【００９３】
巻線中の自己誘導は磁化可能本体またはコアが飽和状態にない限りほぼ直線である。しかし、磁化可能本体の材料中の透磁率の変化を制御磁界によって（すなわち、制御巻線４によって確立された磁界Ｈ２によって）横方向のドメイン磁化を変更することによって自己インダクタンスを変化させる。
【００９４】
式２１と式３１を組み合わせて、

を得る。
【００９５】
自己インダクタンスを伴う電気回路内の交流抵抗ないしリアクタンスは、

によって得られる。
【００９６】
横方向に磁化可能本体中のドメインを磁化することにより、縦方向の磁気抵抗が変化することになる。異なる磁界の影響中にドメインに何が起こるかここでは詳細には説明しない。ここで、ほぼ３％のシリコン含有量を伴う一般的な商業用電気メッキを考慮し、この説明においてメットグラス材料に関する現象の説明を求めることはしないが、これはもちろん本発明を限定することを考慮したものではない。なぜなら、アモルファス構造を伴う磁気材料は、本発明のある適用例で重要な役割を果たすからである。
【００９７】
変圧器において、エネルギが磁気的な漏洩磁界中に、またコア内に少ない量が貯蔵されるが、貯蔵エネルギはエネルギの変換中に直接的な部分を形成せず、結果的にエネルギ変換は電気機械システム内に発生するという観点では生じない、すなわち、電気エネルギが機械エネルギに変換されるが、エネルギは変圧器を通る磁束を介して変換されない高い透磁率を有する閉路コアを使用する。空隙のあるインダクタンス・コイルないしチョークにおいて、空隙中の磁気抵抗はコア中の磁気抵抗に比較して優勢であって、ほぼ全てのエネルギが空隙中に貯蔵される。
【００９８】
本発明による装置において、「仮想」空隙はドメイン中の飽和現象によって発生する。この場合において、エネルギの貯蔵は全コアからなる分布空隙内で発生する。損失のない、従って、いかなる損失も外部要素によって表わされる実際のエネルギ貯蔵システムを考慮する。
【００９９】
ここで使用するエネルギの説明は、エネルギー保存の法則に基づくのもである。
【０１００】
上述した無損失電磁システムの第１法則は、
ｄＷｅｌｉｎ ＝ ｄＷｆｌｄ ３４）
で与えられ、図６参照、
ここに、 ｄＷｅｌｉｎ＝差動電気エネルギ供給
ｄＷｆｌｄ＝磁気的貯蔵エネルギ中の差動変化
【０１０１】
式２６から、

が得られる。
【０１０２】
ここで、インダクタンスは直交磁界ないし制御磁界Ｈ２を通して可変であり、また式３１を式２６に代入して、

を得る。
【０１０３】
システム内の作用は、

従って、

を得る。
【０１０４】
磁気抵抗を変えることができるコアを有し、かつ、主巻線のみを有するシステムに対して、式３５に式３７を代入して、

を得る。
【０１０５】
本発明による装置において、Ｌはμｒの関数として変化し、次に磁化可能本体ないしコア１内の比透磁率は制御巻線４中の制御電流Ｉ２の関数となる。
【０１０６】
Ｌが一定のとき、すなわち、Ｉ２が一定のとき、ｄＬが０に等しいので、部分ｉｘｄＬは無視することができ、従って、磁界エネルギは、

によって与えられる。
【０１０７】
ＬがＩ２によって変化されると、磁界エネルギがＬの変化値の結果として変化することになり、これによって電流Ｉもこれが磁束巻数λによる磁界値に関連しているので変化する。ｉおよびλが可変なので、互いの関数となり、一方非直線関数あり、本発明の説明の域を越える数学が必要となるので、ここでは解を求めることはしない。
【０１０８】
しかし、磁界エネルギとエネルギ分布はμｒによって制御可能であり、また磁界に貯蔵されたエネルギの影響がいかにして増減するかという結論を引き出すことができる。磁界エネルギが減少したときに、過剰部分が発電機に帰還されることになる。あるいは第１主巻線２、またその同じ巻線軸として同じ巻線窓に余分巻線（例えば、図１の巻線３）を設ければ、第１巻線２から第２主巻線３にエネルギの変圧器作用のある変換が提供される。
【０１０９】
これを図７に示し、ここでλの変化は原点でＷｆｌｔ（λ０，ｉ０）である磁界Ｗｆｌｔ内の変化となる。変化はここでは非常に小さいことが予想され、λの変化中ｉはほぼ一定となる。従って、可変インダクタンスを見たときに、次のことが言える。
【０１１０】
どのようなことが生じるかを図８と図９に示す。
【０１１１】
図８は磁化可能本体１の全材料に対する磁化曲線と主巻線２からのＨ１磁界の影響下のドメイン変化を示す。
【０１１２】
図９は磁化可能本体１の全材料に対する磁化曲線と制御巻線４からの方向にあるＨ２磁界の影響下のドメイン変化を示す。
【０１１３】
図１０ａと１０ｂは磁束密度Ｂ１（磁界Ｈ１は作用電流によって確立され）と、Ｂ２（制御電流に対応する）を示す。楕円形はＢ磁界の飽和限界を示す。すなわち、Ｂ磁界がリミットに達したときに、これが磁化可能本体１の材料をして飽和に至らしめることになる。楕円形の軸の形態は磁化可能本体１のコア材料中の二つの磁界Ｂ１（Ｈ１）とＢ２（Ｈ２）の磁路の長さと透磁率によって与えられる。
【０１１４】
図１０に軸を描くことにより、ＭＭＫ分布またはＨ磁界の分布を表わし、図から二つの電流ＩとＩ２による起磁力が確認できる。
【０１１５】
ここで再度図８と９を参照する。制御磁界Ｂ２（Ｈ２）によるドメインの部分的な磁化により、主巻線２からの付加的な磁界Ｂ１（Ｈ１）がベクトル的に制御磁界Ｂ２（Ｈ２）に付加され、ドメインがさらに磁化され、結果として主巻線２のインダクタンスは制御磁界Ｂ２（Ｈ２）の影響下でドメインの状態によって与えられたベースから出発することになる。
【０１１６】
これによってドメインの磁化、インダクタンスＬおよび交流抵抗ＸＬが制御磁界Ｂ２の関数として直線的に変化する。
【０１１７】
残りの図面を参照して本発明に基づく装置の種々の実施例を次に説明する。
【０１１８】
図１１は本発明の第２実施例を概略的に示す。
【０１１９】
図１２は本発明に基づく磁気影響コネクタの同じ実施例を示し、図１２ａは集合されたコネクタを、また図１２ｂは端部から見たコネクタを示す。
【０１２０】
図１３は図１２ｂの線ＩＩから見た断面図である。
【０１２１】
図示したように、磁化可能本体１は特に磁化可能材料から作られた二つの並列管６と７からなる。電気的に絶縁された電導体８（図１２ａ，１３）が、Ｎ巻数の第１管６と第２管７を通る径路内に連続的に通過されている。ここにＮ＝１，．．．ｒで第１主巻線２を形成し、図１３に明瞭に示したように電導体８が二つの管６と７を通る対向方向に延長している。電導体８が第１管６と第２管７を２回通って延長されているのを示しているだけであるが、電導体８をそれぞれの管に１回のみ、または数回（巻き数Ｎは０からｒまで変えることができる）通過させて延長することも可能であるということは自明であり、従って、電導体が励起されたときに平行な管６と７内に磁界Ｈ１を生成することができる。電導体９からなる制御巻線４と磁化巻線４’との組み合わせが第１管と第２管（それぞれ６および７）の回りに巻回されるが、その磁界Ｈ２（Ｂ２）の方向は、巻線４が励起されたときに前記両管が内に発生される磁界Ｈ２（Ｂ２）の方向が、図１１の磁界Ｂ２（Ｈ２）に対する矢印によって指示されたような対向方向となるような方法でなされる。磁界結合器１０、１１は、それぞれの管６、７の両端に、これら両管が磁界方向に相互連結されループをなすように取り付けられている。電導体８は負荷電流Ｉ１（図１２ａ）を流せるようになっている。管６、７の長さと直径は電力と、これに接続しなければならない電圧に基づいて決定される。主巻線２の巻数Ｎ１は電圧の逆阻止能力と作用磁束φ２の範囲にある断面積とによって決定される。制御巻線４の巻数Ｎ２は、両管６、７と磁界結合器１０、１１からなる磁化可能本体１の飽和に必要とされる磁界によって決定される。
【０１２２】
図１４は本発明に基づく装置内の主巻線２の特殊な設計を示す。実際は、図１４の解決策は図１２と１３に示したものとは異なり、両管６と７を通過される単一の絶縁された電導体８の代わりに、二つの分離した対向して向けられた電導体、いわゆる第１電導体８と第２電導体８’が使用され、これによって本発明に基づく磁気誘導型の装置のための電圧コンバータが達成されることは事実である。これについては次に詳細に説明する。この設計は図１１、１２および１３に示したものと基本的には類似している。磁化可能本体１は二つの平行管６および７からなる。電気的に絶縁された第１電導体８が、巻数Ｎ１の第１管６と第２管７を通る径路内に連続的に通過している。ここでＮ１＝１，．．．ｒであり、一次電導体８が二つの管６および７を通って対向方向に延長している。電気的に絶縁された第２電導体８’が、巻数Ｎ１’の第１管６と第２管７を通る径路内に連続的に通過している。ここでＮ１’＝１，．．．ｒであり、第２電導体８’が二つの管６および７を通って第１電導体８に対して対向方向に延長している。少なくとも一つの合成制御巻線４および磁化巻線４’が第１管６と第２管７のそれぞれの回りに巻回され、この結果前記管上に生成された磁界方向が対向する方向を向く。図１１、１２および１３に基づく実施例に関する限り、磁界結合器１０、１１は両管６と７をループ状にし、これによって磁化可能本体１が形成される磁界方向に相互連結するためにそれぞれの管（６、７）の端部に設けられている。単純化する目的で第１電導体８と第２電導体８’を両管６と７を通るただ一つの径路のみを示しているが、第１電導体８と第２電導体８’両方が、それぞれＮ１とＮ１’の巻数で管６および７を通過されていることが直ちに理解できる。管６と７の長さと直径は変換されるべき電力と電圧を基準にして決定される。変換（変圧）比（Ｎ１：Ｎ１’）が１０：１に等しい変圧器において、実際には第１電導体８として１０個の電導体が、そして、ただ１個の電導体が第２電導体８’に使用されている。
【０１２３】
磁界結合器１０および（または）１１の実施例を図１５に示す。磁気的導通材料からなる磁界結合器１０、１１を示すが、ここで主巻線２の電導体８のための二つの好ましい円形アパーチャ１２（例えば、図１３参照）が、コネクタ１０、１１内の磁気材料に機械整形される。さらに、コンダクタ８の磁界径路を断続する空隙１３が設けられている。端面１４がコンダクタ９と９’からなる制御巻線４からの磁束Ｈ２のための結合面になっている（図１３）。
【０１２４】
図１６は本発明の好ましい実施例の管６と７の端面と磁界結合器１０、１１間に配備される薄い絶縁フィルム１５を示す。
【０１２５】
図１７と１８は磁界結合器１０、１１の代わりとなる他の実施例を示す。
【０１２６】
図１９〜３２は図１２、１３および１４に示した実施例のコア１６の種々の実施例を示し、管６と７の主部を形成しているそのコアが磁界結合器１０と１１が一緒になって磁化可能本体１を形成している。
【０１２７】
図１９は図示した長手方向に分割されたシリンダ状コア部材１６を示し、絶縁材料からなる一つまたはそれ以上の層１７が二つのコア半体１６’と１６”間に配置されている。
【０１２８】
図２０は矩形状コア部材１６を示し、また図２１はこのコア部材１６がその横面で二つの部分部材に分割された実施例を示す。図２１に示した実施例において、一つまたはそれ以上の絶縁材料層１７がコア半体１６、１６’間に配備されている。部分部材が各コーナーに配備されている、さらなる変形例を図２２に示す。
【０１２９】
図２３、２４および２５は矩形状のものを示す。図２６、２７および２８は三角形状の同じものを示す。図２９と３０は楕円形状のものを、最後に図３１と３２は六角形状のものを示す。図３１において、六角形状は６個の等しい面１８からなり、また図３２において、六角形は二つの部材１６’と１６”からなる。参照番号１７は薄い絶縁フィルムを示す。
【０１３０】
図３３と３４は矩形および方形主コア１６（それぞれ図２０〜２１および２３〜２５に示す）間の制御磁界結合器として使用することができる磁界結合器１０、１１を示す。この磁界結合器は三つの部材１０’、１０”および１９からなる。
【０１３１】
図３４はコア部材ないし主コア１６の実施例を示し、制御磁束の端面１４または接続面がコア部材１６の軸と直角をなしている。
【０１３２】
図３５はコア部材１６の第２実施例を示し、制御磁束の端面１４がコア部材１６の軸と角度αをなしている。
【０１３３】
図３６〜３８は磁界結合器１０、１１の種々の設計を示し、磁界結合器１０、１１の接続面１４’は、端面１４がコア部材１６に対する角度と同じであるという事実に基づいている。
【０１３４】
図３６は磁界結合器１０、１１を示し、その異なるホール形状１２がコア部材１６の形状（円形、三角形等）に基づいて主巻線２のために指示されている。
【０１３５】
図３７において、磁界結合器１０、１１は平坦である。これは直角端面１４を伴うコア部材１６と併用されるように適用されている。
【０１３６】
図３８において、角度α’は磁界結合器１０、１１に対して指示され、角度αがコア部材（図３５）に対して適用され、従って、端面１４と接続面１４’が一致する。
【０１３７】
図３９において、本発明の実施例は磁気コネクタ１０、１１とコア部材１６の集合体を示す。図３９ｂは側部から見た同じ実施例を示す。
【０１３８】
磁界結合器とコア部材のそれぞれの組み合わせのみを本発明を示すために説明されているが、当該技術に習熟した人にとって明白であるように、他の組み合わせもまったく可能であり、従って、本発明の概念内に入る。
【０１３９】
制御巻線と主巻線の位置を切り替えることも可能である。
【０１４０】
図４０と４１は磁気誘導型の電圧コネクタ装置の第３実施例のそれぞれ断面図と平面図である。この装置は（図４０ｂ参照）外部管２０と内部管２１（またはコア部材１６、１６’）からなる磁化可能本体１からなる。両管は同心をなすとともに磁化可能材料から作られ、外部管２０の内壁と内部管２１の外壁間に空隙２２を備えている。管２０と管２１間の磁界結合器１０、１１はそれぞれの端部（図４０ａ）に取り付けられている。スペーサ２３（図４０ａ）が空隙２２内に配備されていて、両管２０、２１を同心に維持している。電導体９からなる組み合わされた制御／磁化巻線４が内方管２１の回りに巻回されるとともに前記空隙２２内に配備されている。従って、制御巻線の巻線軸Ａ２は両管２０と２１の軸Ａ１と一致している。電導体８からなる電流供給巻線ないし主巻線２が内方管２１を通り、かつ、Ｎ１＝１，...rであるＮ１回数の外方管２０の外部に沿って通過している。主巻線２または前記電流供給電導体８と共動する合成制御／磁化巻線４により、容易に構成されるが効果的に磁気的に影響を受ける電圧コネクタが得られる。装置のこの実施例は両管２０、２１が円形断面ではなく、方形、矩形、三角形等の断面を有するような方法で変形することもできる。
【０１４１】
主巻線を内方管２１の回りに巻回することもでき、この場合主巻線の軸Ａ２は両管の軸Ａ１と一致し、一方制御巻線が管２１の内方と管２０の外方で両管の回りに巻回される。
【０１４２】
図４２〜４４は磁界結合器１０、１１の種々の実施例を示す。特に本発明の後者の設計、すなわち、図４０と４１に関して説明したものに適している。
【０１４３】
図４２ａは磁界結合器１０、１１の断面を示し、また図４２ｂはその平面を示し、接触面１４’が両管２０、２１（コア部材１６）の軸に関してある角度があり、内方管２１と外方管２０は接触面１４に対して同じ角度にあることは明らかである。
【０１４４】
図４３と４４は磁界結合器１０、１１の他の変形例を示し、制御磁界Ｈ２（Ｂ２）の接触面１４’がコア部材１６（両管２０、２１）の主軸に対して垂直をなしている。図４３は中空半円形断面を有する中空半環状磁界結合器１０、１１を示し、一方図４４は矩形断面を有する環状磁界結合器を示す。
【０１４５】
図４０と４１に示した装置の変形例を図４５に示し、ここで図４５ａは側部から見た装置を示し、一方図４５ｂはその上方から見た図を示す。図４０〜４１の電圧コネクタとの単なる差異は、第２主巻線３が主巻線２として同じコースに巻回されていることである。これによって、容易に構成でき、効果的な磁気的に影響を受ける電圧コンバータが得られる。
【０１４６】
図４６と４７は、同心管を備えた電圧コネクタの第４実施例の断面図と平面図である。
【０１４７】
図４６と４７は、結合コアを備えた電圧コンバータとして作用する電圧コネクタを示す。内方磁気抵抗制御コア２４が、主巻線２の巻回された外方コア２５内に配備されている。内方磁気抵抗制御コア２４は図４０と４１の説明下に上述したのと同じ構造を有しているが、ただ一つの差異はコア２４の回りに主巻線２がないことである。内方磁気抵抗制御コア２４を形成する内方部材２１と外方部材間の空隙２２内に制御巻線４が配置されていることだけである。この結果、コア２４のみが制御巻線４内の電流からの制御磁界Ｈ２（Ｂ２）の影響下で磁気的に磁気抵抗制御される。
【０１４８】
図４６と４７の主巻線２は、コア２４とコア２５両方を包み込む巻線である。
【０１４９】
本発明に基づき、図４６と４７に関して説明した磁気抵抗制御電圧コネクタないしコンバータの動作のモードを次に説明する。
【０１５０】
結線の原理を示す図５５も参照し、図６５は磁気抵抗モデルの簡略化等価回路図であり、Ｒｍｈは巻線２と３間の磁束を制御する可変磁気抵抗であり、また図６５ｂはＬｋが可変インダクタンスである結線とした等価回路を示す。
【０１５１】
巻線２に印加される交流電圧Ｖ１は、巻線２内の磁化電流Ｉ１を確立する。これはコア２４と２５内の磁束φ１＋φ１’によって発生され、これはファラデーの法則に基づいて巻線２内に発生される阻止電圧を提供するために確立されるのに必要である。制御電流が磁気抵抗制御コア２４内にないときは、磁束はそれぞれのコア２４と２５内の磁気抵抗に基づいてコア２４と２５間で分割される。
【０１５２】
一つの巻線から他の巻線にエネルギを移すために、内方磁気抵抗制御コア２４が制御電流Ｉ２の供給を受けなければならない。
【０１５３】
巻線２内の交流電圧Ｖ１の正半周期に制御電流Ｉ２を供給することにより、巻線２に半周期電圧を得る。エネルギが磁気抵抗制御コア２４と外方（第２）コア２５間の磁束変位によって変換されるので、磁気抵抗制御コア２４はこれが飽和中に制御されている周期中、制御電流Ｉ２によって本質的に影響を受け、一方作用磁束が第２外方コア２５を通過し、エネルギ転送中に一次巻線２と相互作用する。
【０１５４】
磁気抵抗制御コア２４が、作用磁束Ｂ１（Ｈ１）と直交する制御磁束Ｂ２（Ｈ２）をリセットすることによって飽和されたときに、一次側からの磁束が再度コア２４と２５間で分割され、また二次巻線３に接続された負荷が低磁気抵抗となり、これによって高いインダクタンスと、一次（ＶＩ）と二次（Ｖ３）電圧間に小さい結合を見るだけである。電圧が二次巻線３に発生されるが、磁化インピーダンスＬｍと比較したＬｋの大きさを考慮すると、一次巻線２からの電圧（Ｖ１）のほとんどがＬｋをオーバーレイする。一次巻線２からの磁束は本質的に最も小さい磁気抵抗を通り、磁路が最短になる（図６５ｂ）。
【０１５５】
外方コア２５は制御可能に作れることが予想でき、さらに第４主巻線を内方制御可能コア２４の回りに巻回される。これはコア２４と２５間の電圧を必要に応じて制御可能にする。
【０１５６】
図４８は本発明に基づく磁気的に影響を受ける電圧コネクタないし電圧コンバータの第４実施例のさらなる変形例を示し、磁化可能本体１は制御磁束Ｂ２（Ｈ２）が別体の磁界結合器なしに主コア１６に直接接続されるように設計される。
【０１５７】
図４８は側面から見て環状の形態にある電圧コネクタを示す。この電圧コネクタは二つのコア部材１６と１６’、主巻線２および制御巻線４からなる。
【０１５８】
図４９は電圧変換の能力を提供するエキストラ主巻線３を備えた本発明に基づく電圧コネクタを示す。
【０１５９】
図５０は図４８の線ＶＩ〜ＶＩから見た断面による図４８の装置を示し、図５１は線Ｖ〜Ｖから見た断面を示す。図５０において、円形アパーチャ１２は制御巻線４を配置するために示されている。
【０１６０】
図５１は配線を通過するための付加アパーチャ２６を示す。
【０１６１】
図５２と５３は巻線のないコア構造を示し、コア１６は制御磁界のための余分な磁界結合器を必要としない設計になっている。コア１６は二つのコア部材１６、１６’および制御巻線４のためのアパーチャ１２を有している。この設計は、磁気材料が燒結ないし圧縮モールド材料を使用することを意図している。この場合において、閉磁路をトポロジー内に挿入することが可能となり、この結果箔巻コアに必要としたこれまでの別体のコネクタが、実際のコアの部品を形成し、構造の生産的パーツになる。別体の磁界結合器のない閉磁路を形成し、かつ、図５２と５３に示したコアは、たとえ本体１が本発明の第１実施例に適用されると図示（特に、図１と２に示された）されていたとしても、本発明の全ての実施例に使用することが可能になる。
【０１６２】
図５４は磁気的に影響を受ける電圧コンバータ装置を示し、ここで装置は外方管２０と内方管２１からなる内方制御コア２４を有している。両管は同心をなすとともに外方管２０の内壁と内方管２１の外壁間に空隙２２を備えた磁化可能材料から作られている。スペーサ２３が外方管２０の内壁と内方管２１の外壁間の空隙に挿入されている。磁界結合器１０、１１は管２０と２１の間にそれぞれの端部に取り付けられている。合成制御磁化巻線４が内方管２１の間回りに巻回されるとともに前記空隙２２内に配備されている。この装置はさらに制御コア２４の外側に配置された複数のリング・コア・コイル２５’、２５”、２５’’’等からなる巻線を備えた外方第２コア２５からなる。各リング・コア・コイル２５’、２５”、２５’’’等はそれぞれの主巻線ないし第２巻線３によって回りに巻回された磁化可能材料のリングからなり、図を明瞭にする目的でただ一つのみを示す。第１主巻線ないし一次巻線２が制御コア２４内に内方管２１を、また、Ｎ１＝１，．．．ｒであるＮ１回数の外方コア２５の外側に沿って通過している。
【０１６３】
第２コア装置を制御巻線２４内に配備することも考えられ、この場合一次巻線２はリング・コア２５を通過し、制御コア２４の外側に沿って通ることになる。
【０１６４】
図５５は第１磁気抵抗制御コア２４と第２コアを備えた本発明に基づく磁気的に影響を受ける電圧調整器の第２実施例の概略図であり、各々磁化可能材料で構成され、閉磁気回路を形成するように設計され、前記コアは併置されている。少なくとも一つの第１電導体８が前記閉回路の少なくとも一部に沿って第１および第２コア断面プロフィール両者の回りに主巻線２上に巻回されている。少なくとも一つの第２電導体９が閉回路に本質的に対応する形態に磁気抵抗制御コア２４内の巻線４として取り付けられている。付加的に、少なくとも一つの第３電導体２７が第２コアの断面形態の回りに閉回路の少なくとも一部に沿って巻回されている。第１電導体の巻線２と第２電導体９の巻線の磁界方向は直交している。この解決策により、第１電導体８と第３電導体２７が、それぞれ一次巻線２と二次巻線３を形成している。
【０１６５】
図５６は本発明に基づく電圧コネクタのための電気−機械的概略シンボルの提案を示す。図５７は電圧コネクタのための概略ブロック・シンボルの提案を示す。
【０１６６】
図５８は制御巻線４と制御磁束Ｂ２（Ｈ２）を含まない磁気回路を示す。
【０１６７】
図５９と６０において、電圧コンバータのための電気−機械的概略シンボルの提案を示し、制御コア２４の磁気抵抗が固定磁気抵抗２５と可変磁気抵抗を伴う第２コア２４間で磁束がシフトしている（例えば、図５５を参照）。
【０１６８】
もちろん、二つのコアを可変磁気抵抗を有することに限定しない。同じ巻線内で二つのコア間で磁束をシフトできるという事実は、主コア内の磁化のコースと独立して電圧をオンオフする磁気スイッチを作るために使用することができる。これはＧＴＯとして同じ機能を有するスイッチを、所望するスイッチ時間をいつでも選択できることを除けば作れることを意味する。
【０１６９】
本発明に基づく装置は多数の異なる結線に使用することができ、また例として特に適切と思われる適用例を次に説明する。
【０１７０】
図６１は光源、熱源または他の負荷となる負荷ＲＬに対する電圧を制御するための交流回路内への本発明の使用状態を示す。
【０１７１】
図６２は３相システムへの本発明の使用を示し、ここでダイオード・ブリッジに接続された各相のこの種の電圧コネクタがダイオード・ブリッジからの出力電圧の直線調整のために使用される。
【０１７２】
図６３はＤＣ−ＤＣコンバータ内に可変チョークとしての使用を示す。
【０１７３】
図６４はコンデンサと一緒にフィルタ内の可変チョークとしての使用を示す。ここで、直列および並列フィルターのみを示す（それぞれ図６４ａと６４ｂ）が、可変インダクタンスは多数のフィルター・トポロジーに使用することができることは暗に示されている。
【０１７４】
本発明のさらなる適用例は、特に図１４と１５に関連して説明するが、概略的なシンボルの提案は図５９に示している。この適用例において、電圧コネクタは二次巻線を付加した電圧コンバータとしての機能を有している。電圧調整器としての適用例もここに図示し、変圧器結線と漏れリアクタンスが制御巻線４を介して制御可能である。このシステムの特別な特徴は、変圧器の式が適用できることであり、一方でこれと同時に磁化電流がμｒの変更によって制御できることである。従って、この場合において、変圧器の特徴がある程度まで調整できる。一つの巻線２のＤＣ励起があれば、変圧器による変換エネルギをμｒ、従って、励起の変化の代わりに磁気抵抗制御コア内の磁束の変化によって得ることができる。従って、ＤＣ発電機からこのシステムへの磁化電流の変化が二次側の巻線に転換できるという事実によってＤＣ電圧からＡＣ電圧を発生することが原理的に可能である。
【０１７５】
本発明の別の適用例を図４６と４７に示す。ここで制御コアとしての可変磁気抵抗が、分離巻線を伴う一つまたはそれ以上の分離コアによって取り巻かれているかまたは収容されている。図５５にも示すように、第１磁気抵抗制御コアと第２コアが閉磁路として設計され、併置されている。等価電気回路を示す図６５も参照する。
【０１７６】
図５５は本発明の磁束がいかにコア内を進行するかを示す。制御コア内の磁束が両コアを収容する巻線を介して作用コア内の磁束に結合されることを強調したい。このシステムにおいて、電気エネルギの転換は制御コアと作用コアとの間で断続される磁束によって制御可能となる。両コア間の磁束がファラデーの誘導法則によって相互結合されるので、一次側の式と二次側の式の関数関係は両磁束間の結合によって制御されることになる。線型的な適用において、一次巻線と二次巻線間の電圧および電流の転換を制御コア内の磁気抵抗を変えることによって制御でき、従って、ここで磁気抵抗制御変圧器の項を持ちこむことが許される。スイッチの実施例に対しては、磁気抵抗制御スイッチの項を導入することができる。
【０１７７】
一次ないし第１主巻線２と二次巻線ないし第２主巻線３間の磁束結合について次に説明する。磁気抵抗制御される制御コア２４とコア２５両方にここで収容された巻線２が両コア内で磁束を確立する。電流Ｉ１が（巻線）２に通過したときに自己インダクタンスＬ１から（巻線）２が、どれだけの大きさの磁束であるか、または何本の磁束ターンがコア内で生成されたかを示す。一次巻線２と二次巻線３間の相互インダクタンスが２によって確立された磁束ターンがどれだけあるかを指示し、またＩ１が巻線２の回りと二次巻線３の回りにターンされている状態を示す。
【０１７８】
もちろん、主コア２５が磁気抵抗制御されると予想されるが、簡略にする目的でここでは磁気抵抗が一定である主コア２５と、磁気抵抗が可変である制御コア２４を伴うシステムを参照することにする。
【０１７９】
磁束線は最大のパーミアンス（透磁率が最大）、すなわち最大の磁気抵抗を呈する径路を追従する。
【０１８０】
図５５と６５において、主巻線２と３内の漏洩磁界は考慮していない。図５５は一次巻線２と二次巻線３が各々変圧器脚の回りに巻回された変圧器の簡略化モデルを示し、一方実際には両巻線は同じ変圧器脚に巻回されるのが好ましく、この場合、例えば主コア２５内の外方リング・コアは全コア２５に沿って分布された二次巻線３の回りに巻回される。同様にして、一次巻線２は主コア２５と、主コア内に同心に配備された制御コア２４の回りに巻回される。
【０１８１】
図６５は本発明に基づく装置のための簡略化磁気抵抗モデルを示す。
【０１８２】
図６５ａは本発明に基づくコネクタのための簡略化電気等価回路を、磁気抵抗をインダクタンスに置換して示している。
【０１８３】
一次巻線２内の電流がコア２４と２５内で磁束を発生する：

ここに：
Φｐ ＝巻線２内の電流によって確立された総磁束
Φｋ ＝制御コア２４を通って進行する総磁束
Φｌ ＝主コア２５を通って進行する総磁束の一部
主コア２４と制御コア２５内の漏洩磁束が無視されるので、

多少、Φｋは制御された漏洩磁束と見なすことができる。
【０１８４】
図６５に基づいて、図６５ｂに示した磁気回路のための大々的に簡略化した電気等価回路を公式化することができる。
【０１８５】
従って、図６５ｂは磁気抵抗制御結合器の原理を示し、ここでインダクタンスＬｋ が一次側からの電圧を吸収する。

【０１８６】
このインダクタンスは制御コア２４内の可変磁気抵抗によって制御され、この結果、一次巻線に印加される正弦波定常電圧のために結線ないし電圧分割が式４３に示したようにそれぞれのコア内のインダクタンス間の比にほぼ等しくなる。

【０１８７】
制御コア２４が飽和されたときに、ＬｋがＬｍと比較して非常に小さく、また電圧分割が巻数Ｎ１／Ｎ３間の比に基づくことになる。制御コアがオフ状態にあるとき、Ｌｋが大きく、また同じ範囲で二次側への電圧転換が阻止される。
【０１８８】
印加電圧と周波数に関する両コアの磁化状態は、主コア２５と制御コア２４が飽和に至るこをなしに各々別々に全時間電圧積分を吸収するように評価される。このモデルにおいて、制御コアおよび作用コアの鉄の面積が等しいが、これは本発明を限定することを考慮するのもではない。
【０１８９】
制御コア２４が主巻線２のために飽和状態にならないので、制御コア２４を作用磁束Ｂ１（Ｈ１）と独立してリセットすることができ、これによって磁気スイッチを実現する本発明によって目的を達成できる。必要ならば、磁化電流内のひずみを補正するためにのみ主コア２５は、必要なＭＭＦが第２半周期に戻るまでの１パルスまたは周期の半分後でリセットできる。
【０１９０】
切換適用例において、スイッチがオフのとき、すなわち、一次巻線２の磁束が制御コア２４と作用コア２５間に分布されているときに、一次巻線２と二次巻線３間の磁束結合は僅かであり、非常に小さいエネルギ転換が一次巻線２と二次巻線３に発生される。
【０１９１】
スイッチがオンのとき、すなわち、制御コア２４内の磁気抵抗が非常に小さく（μｒ＝１０〜５０）、また、空気コイルの磁気抵抗に近づいたときに、一次巻線２と二次巻線３の間で非常に優れた磁束結合とエネルギの転換を得ることになる。
【０１９２】
従って、本発明の重要な適用例は、磁気抵抗制御スイッチおよび従来の周波数コンバータ結線および整流器結線に磁気抵抵制御スイッチを使用するＤＣ−ＡＣまたはＡＣ−ＤＣコンバータを備えた周波数コンバータとしたものである。
【０１９３】
周波数コンバータの変形例が、３相システム中の各相から小さい正弦電圧を付加することによって実現することが考えられ、各々分離磁気抵抗制御コアに接続され、これが次に付加コアと磁気抵抗制御コアを介して共通巻線によって磁気抵抗制御コアに磁気的に結合された一つまたはそれ以上の付加コアに結合されている。次に正弦電圧の一部が磁気抵抗制御コアから付加コアに接続され、異なる周波数の電圧が発生される。
【０１９４】
ＤＣ−ＡＣコンバータがＤＣ電圧を作用コアに収容される主巻線に接続することによって実現でき、この時点で作用コアは二次巻線の回りに巻回され、作用コアと制御コア間の磁束結合を正弦波的に変化させることによって正弦電圧を得ることができる。
【０１９５】
図６６は磁気スイッチのための結線を示す。もちろん、これは調整可能変圧器としても作用する。
【０１９６】
図６７および６７ａは３相設計の一例を示す。もちろん、全ての他の３相整流器結線も可能である。ダイオード・ブリッジまたはそれぞれのダイオードを１２パルス・コネクタ内のそれぞれのアウトレットに接続することにより、調節可能な整流器が得られる。
【０１９７】
調節可能変圧器としての適用例において、磁気抵抗制御コアの寸法は（０〜１００％または８０〜１１０％の）電圧のための変圧器が必要とされる調節の範囲によって決定されることを強調しなければならない。
【０１９８】
図６７ｂは入力周波数を、無作為に選択された出力周波数に変換するための周波数変換器内のコネクタとして、また６または１２パルスの変圧器から発生された相電圧の一部を各電動機位相に付加するための非同期電動機の作動を意図した本発明に基づいた装置の使用を示す（６７ｂ）。
【０１９９】
図６８はＵＦＣ（強制整流による無制限周波数変換装置）内のスイッチとして使用される装置を示す。
【０２００】
図６９は本発明に基づく６台の装置２８〜３３からなる回路を示す。装置２８〜３３は周波数コンバータとして使用され、発生された電圧の周期は基本周波数の一部からなる。これは正の新しい半周期を新しい正弦電圧内に形成し、続いて負の半周期または負の半周期の一部を形成するために正弦電圧の正半周期または半周期の一部のみを「通過させ」、これによって新しい正弦電圧内に負の半周期を形成することにより作動する。この方法において、正弦電圧は基本周波数の１０％から１００％の周波数で発生される。このコンバータは、出力の電圧が一次巻線と二次巻線間の結線の磁気抵抗制御を介して調整されるので、ソフト始動として作動する。
【０２０１】
図６９において、最初の半周期がコネクタ番号２８（主巻線２）によって許容されれば、同じコネクタ中の二次巻線（主巻線３）を流れる電流がコネクタ番号２９中の二次巻線（主巻線３）を整流し、また２９から２８へ等々順になされる。
【０２０２】
図７０は本発明に基づく装置のＤＣ−ＡＣコンバータとしての使用を示す。ここでコネクタ中の主巻線２がＤＣ電圧Ｕ１によって励起される。この電圧は制御コア２４と主コア２５（図には示していない）両方に磁界Ｈ１（Ｂ１）を確立する。ターン数Ｎ１、Ｎ２、Ｎ３および鉄の面積は、どのコアも定常状態で飽和しないような方法で設計される。制御信号（すなわち、制御巻線４の励起）の制御コア２４への伝送の事象において、その磁束Ｂ２（Ｈ２）が主コア２５へ転送され、またこのコア２５内で磁束Ｂ１（Ｈ１）内の変化が二次巻線（主巻線３）内に電圧を誘起するような方法で設計される。正弦状制御電流Ｉ２を有することにより、正弦電圧が制御電圧Ｕ１として同じ周波数で二次側（主巻線３）上に発生可能である。
【０２０３】
図７０ｂは磁気抵抗の変化を伴うコンバータとして本発明の使用を示す。
【０２０４】
図７１はＡＣ−ＤＣコンバータとして本発明に基づく装置の使用を示す。同じ制御原理が、図６９の周波数コンバータの説明中に上述したようにここでも使用される。図７１ｂは装置の入力と出力電圧の時間の図を示す。
【０２０５】
上述したように、本発明に基づく電圧コネクタは、発電機と負荷間で電圧の吸収のための可動部が実質上ない。コネクタの機能は発電機と負荷間の電圧を小さい制御電流によって０〜１００％で制御できることである。第２機能は単に電圧スイッチとなることである。さらなる機能は電圧曲線を形成し、転換できることである。
【０２０６】
本発明に基づく新しい技術は、既存のダイオード整流器をアップグレードさせるために使用することができるが、調整が必要である。１２パルスまたは２４パルスの整流システムに関して、０〜１００％の制御可能な整流を保持しながら簡単な方法でシステム内の電圧を平衡させることができる。
【０２０７】
本発明に包含される磁気材料に関して、費用／利益要素を基準にして選択される。費用は市場における利用性、選択された種々の解決策の生産性および価格のうないくつかのパラメータとリンクしている。利益要素は、電気技術要素に基づいており、材料は材料のタイプおよび磁気特性を含めて必要である。重要であると考えられる磁気特性にはヒステリシス損、飽和磁束レベル、透磁率、材料の二つの主要方向における磁化容量および磁気ひずみが含まれる。本発明に包含されるエネルギ源とユーザへの電気ユニット周波数、電圧と電力が、材料の選択をするために決定される。適切な材料には次のものが含まれる：
ａ）鉄−シリコン・スチール：厚みが約０．１ｍｍ〜０．３ｍｍ、幅が１０ｍｍから１１００ｍｍ片として成され、コイルに巻き取られる。おそらく、価格と既に開発された製造技術を考慮して大きいコアが最も好ましい。低周波数で使用するためである。
ｂ）鉄−ニッケル合金（パーマロイ）および（または）鉄−コバルト合金（パーメンジュール）、片として生成されコイルに巻き取られる。これらは特殊な磁気特性を備えた合金であり、そのサブグループは開発された非常に特殊な特性を有している。
ｃ）アモルファス合金、メタグラス：厚みが約２０μｍ〜５０μｍ、幅が４ｍｍから２００ｍｍ片として成され、コイルに巻き取られる。非常に高い透磁率、非常に低い損失がほぼ０の磁気ひずみで作られることができる。鉄を基準にしたもの、コバルトを基準にしたもの等、無数の種類が存在する。すばらしい特性であるが高価。
ｄ）ソフト・フェライト：コンバータ工業のために開発された特定形態の燒結体。小さい損失のため高周波数で使用される。低磁束密度。低損失。物理的信頼できる寸法に制限がある。
ｅ）圧縮粉体コア：特定適用例のために開発された特定形状の圧縮鉄粉合金。低透磁率、現在最高約４００〜６００。低損失、しかし高い磁束密度。非常に複雑な形状に生成できる。
【０２０８】
全ての燒結体、プレス−モールド・コアが、実際の形状を閉磁路が適切な磁界のために得られる方法で作ることができるので、特殊な磁界結合器を必要とせずに本発明に関して適切なトポロジーを実行することができる。
【０２０９】
コアがロール状のシート金属に基づいて製作されれば、コアは一つまたはそれ以上の磁界結合器によって補完されなければならない。
【図面の簡単な説明】
【図１】 図１は、本発明の基本原理およびその第１実施例を示す図。
【図２】 図２は、本発明の基本原理およびその第１実施例を示す図。
【図３】 図３は、本発明に基づく装置の実施例の概略図。
【図４】 図４は、本発明に基づく装置の部分を形成する異なる磁束のエリアを示す図。
【図５】 図５は、本発明に基づく装置の第１等価回路図。
【図６】 図６は、本発明に基づく装置の簡単化ブロック図。
【図７】 図７は、磁束対電流を示す図。
【図８】 図８は、本発明に基づく装置の磁気材料のための磁化曲線およびドメインを示す図。
【図９】 図９は、本発明に基づく装置の磁気材料のための磁化曲線およびドメインを示す図。
【図１０】 図１０は、主巻線および制御巻線のための磁束密度を示す図。
【図１１】 図１１は、本発明の第２実施例を示す図。
【図１２】 図１２は、本発明の同じ第２実施例を示す図。
【図１３】 図１３は、第２実施例を断面で示す図。
【図１４】 図１４は、第２実施例を断面で示す図。
【図１５】 図１５は、本発明の前記第２実施例の磁界結合器の異なる実施例を示す図。
【図１６】 図１６は、本発明の前記第２実施例の磁界結合器の異なる実施例を示す図。
【図１７】 図１７は、本発明の前記第２実施例の磁界結合器の異なる実施例を示す図。
【図１８】 図１８は、本発明の前記第２実施例の磁界結合器の異なる実施例を示す図。
【図１９】 図１９は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２０】 図２０は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２１】 図２１は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２２】 図２２は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２３】 図２３は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２４】 図２４は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２５】 図２５は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２６】 図２６は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２７】 図２７は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２８】 図２８は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図２９】 図２９は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図３０】 図３０は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図３１】 図３１は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図３２】 図３２は、本発明の第２実施例の管状本体の異なる実施例を示す図。
【図３３】 図３３は、本発明の第２実施例の磁界結合器の異なる観点を示す図
【図３４】 図３４は、本発明の第２実施例の磁界結合器の異なる観点を示す図
【図３５】 図３５は、本発明の第２実施例の磁界結合器の異なる観点を示す図
【図３６】 図３６は、本発明の第２実施例の磁界結合器の異なる観点を示す図
【図３７】 図３７は、本発明の第２実施例の磁界結合器の異なる観点を示す図
【図３８】 図３８は、本発明の第２実施例の磁界結合器の異なる観点を示す図
【図３９】 図３９は、本発明の第２実施例に基づいて組み立てた装置を示す図。
【図４０】 図４０は、本発明の第３実施例の断面図および平面図。
【図４１】 図４１は、本発明の第３実施例の断面図および平面図。
【図４２】 図４２は、本発明の第３実施例に使用するための磁界結合器の特定実施例を示す図。
【図４３】 図４３は、本発明の第３実施例に使用するための磁界結合器の特定実施例を示す図。
【図４４】 図４４は、本発明の第３実施例に使用するための磁界結合器の特定実施例を示す図。
【図４５】 図４５は、変圧器として使用するために本発明の第３実施例を示す図。
【図４６】 図４６は、磁気抵抗制御磁束結合変圧器として使用するために本発明の第４実施例の断面図および平面図。
【図４７】 図４７は、磁気抵抗制御磁束結合変圧器として使用するために本発明の第４実施例の断面図および平面図。
【図４８】 図４８は、粉体基準磁気材料に合うように適用され、これによって磁界結合器のない本発明の第４実施例を示す図。
【図４９】 図４９は、粉体基準磁気材料に合うように適用され、これによって磁界結合器のない本発明の第４実施例を示す図。
【図５０】 図５０は、図４８の線ＶＩ−ＶＩから見た断面図。
【図５１】 図５１は、図４８の線ＶＩ−ＶＩから見た断面図。
【図５２】 図５２は、粉体基材磁気材料に合うように適用され、これによって磁界結合器のないコアを示す図。
【図５３】 図５３は、粉体基材磁気材料に合うように適用され、これによって磁界結合器のないコアを示す図。
【図５４】 図５４は、本発明の第４実施例の変形例の「Ｘ線写真」図。
【図５５】 図５５は、変圧器結線のための可能性を背景にした原理を共にした本発明に基づく装置の第２変形例を示す図。
【図５６】 図５６は、本発明に基づく電圧コネクタのための電気−機械的概略シンボルの提案を示す図。
【図５７】 図５７は、電圧コネクタのためのブロック概略シンボルのための提案を示す図。
【図５８】 図５８は、制御巻線および制御磁束を含まない磁気回路を示す図。
【図５９】 図５９は、本発明に基づく電圧コンバータのための電気−機械的概略シンボルの提案を示す図。
【図６０】 図６０は、本発明に基づく電圧コンバータのための電気−機械的概略シンボルの提案を示す図。
【図６１】 図６１は、交流回路に本発明を使用する図。
【図６２】 図６２は、３相システムに本発明の使用を示す図。
【図６３】 図６３は、ＤＣ−ＤＣコンバータに可変チョークとしての使用を示す図。
【図６４】 図６４は、コンデンサと一緒にフィルター内に可変チョークとしての使用を示す図。
【図６５】 図６５は、本発明に基づく装置のために簡略化した磁気抵抗モデルおよび本発明に基づくコネクタのための簡略化電気等価図を示す図。
【図６６】 図６６は、磁気スイッチのための結線を示す図。
【図６７】 図６７は、本発明の３相使用の例を示す図。
【図６８】 図６８は、スイッチとして使用された装置を示す図。
【図６９】 図６９は、本発明に基づく６台の装置からなる回路図。
【図７０】 図７０は、ＤＣ−ＡＣ変換器として本発明に基づく装置の使用を説明する図。
【図７１】 図７１は、ＡＣ−ＤＣ変換器として本発明に基づく装置の使用を説明する図。[0001]
(Technical field)
The present invention provides a magnetically induced current or voltage regulator and a magnetically affected converter (conversion) for controlled connection and disconnection with electrical energy distribution as disclosed in the introductory part of the attached independent claim. )).
[0002]
(Background technology)
The present invention, an extension of known transducer technology, is particularly suitable for voltage connectors, current regulators or voltage converters in several areas of the field of power electronics. It is particularly characterized that the transformer characteristic or inductive coupling between the control winding and the main winding is almost zero and the inductance of the main winding can be adjusted by the current in the control winding. Furthermore, the magnetic coupling between the main winding and the secondary winding in the transformer form can be adjusted by the current in the control winding.
[0003]
For example, in the rectification field, the present invention can be used in connection with regulating the high voltage input of a large rectifier, where the advantage is full utilization of the diode rectifier over the entire voltage range. With respect to asynchronous motors, the use of the present invention can be observed for a gentle start of a high voltage motor. The invention is also suitable for use in the field of power distribution relating to voltage regulation of power lines, and can also continuously control and compensate reactive power in the network.
[0004]
Even if no restrictions are considered for the use of the device, it can form part of a frequency converter, for example to convert the input frequency to a randomly selected output frequency, preferably intended for the operation of an asynchronous motor Here, the input side of the frequency converter has a three-phase supply source, and its phase conductor supplies the input to at least one transformer intended for each of the converter's three-phase outputs, The outputs of such transformers are connected to each other via a selected controllable voltage connection or via an additional transformer coupling voltage connection.
[0005]
A second application of the device is as a direct converter of DC voltage, whereby the AC voltage frequency can be adjusted continuously.
[0006]
The use of this type of frequency converter in subsea conditions, particularly in the deep seas, necessitates a high-capacity pump that involves shifting. The pumping operation in the underwater system is generally performed from the underwater condition to the sea level position (push-up), and is performed by injecting seawater into the storage device from the underwater condition.
[0007]
Variable speed engine controllers are usually based on two principles. That is, with a) direct electronic frequency tuning converters and b) AC-DC-AC converters with pulse width modulation and with expanded use of semiconductors such as thyristors and IGBTs. The latter is widely used for industrial applications and is also used for board locomotives.
[0008]
Speed control has recently been introduced for motors in underwater environments. The main challenge is the packing and operation of this type of system. In this situation, the operation is directed to service, maintenance, etc. Complex electronic systems generally must be operated in a controlled environment with respect to temperature and pressure. Such a sea-based system must be encapsulated in a nitrogen-filled container that maintains a pressure of 1 atm. Considering the heat generation due to heat loss in the electronic element, a considerable amount of heat will be generated, thus resulting in the need for forced air cooling. This is usually solved by the use of a fan. This fan greatly reduces the service life of the system and introduces elements that indicate a very inappropriate solution.
[0009]
The sensitivity of the electronic element and the electronic power semiconductor is high, and a protection circuit is required. This complicates the system and raises the price.
[0010]
At considerable depths (greater than 300 meters), the containers of this type of system are very heavy and will account for a fairly extreme proportion of the total weight of the system. In addition, system maintenance often requires generation on the entire frequency converter. This is because even simpler maintenance is difficult to perform on a remotely operated vehicle (ROV).
[0011]
(Disclosure of the Invention)
Accordingly, a common object of the device according to the invention is to provide the possibility of providing a frequency converter suitable for submersible pump operation, in particular focusing on operational reliability, stability and minimum maintenance conditions. Operating conditions are about 25 years at a depth of 3000 meters.
[0012]
Standard frequency converters based on semiconductor technology convert alternating current (AC) power with a given frequency into alternating power at other selected frequencies without any intermediate DC connections. The conversion is performed by forming a connection between a given input and output terminal during the adjusted time interval. An output voltage waveform with output frequency F0 is generated between the terminals by concatenating selected portions of the voltage waveform of the AC input source with input frequency F1 in sequence. Such frequency converters exist in the form of standard symmetric synchro converter circuits that supply power from a three-phase network to a three-phase motor. The standard synchro converter module consists of a dual converter within each motor phase. Thus, the usual method uses three identical, essentially independent dual converters to provide a three phase output.
[0013]
Another known frequency converter is a symmetrical 12-pulse central cycloconverter, which consists of a 4-part 12-pulse central converter, each with an output phase. All three converters share a common secondary winding for the input transformer. The neutral conductor can be omitted for balanced three-phase load Y-connected motors.
[0014]
Another known frequency converter based on semiconductor technology is a so-called symmetric 12-pulse bridge circuit, which has three identical quadrant 12-pulse bridge converters each having an output phase. Each input terminal of each of the six 6-pulse converters is supplied from a separate secondary winding of the input transformer. Note that it is not allowed to use the same secondary winding for more than one converter. This is due to the fact that each 12-pulse converter itself requires two fully isolated transformer secondary windings.
[0015]
Thus, although it has been made secondary, the essential purpose of the present invention nevertheless is to avoid the main semiconductor elements of the frequency converter which must be placed at a considerable depth, and this purpose. For this reason, this use was proposed based on the present invention, which is a novel magnetic converter technology based on a totally unconventional concept.
[0016]
(Best Mode for Carrying Out the Invention)
Accordingly, the present invention comprises a magnetic induction type current or voltage regulator, the first embodiment of which comprises a magnetizable material and provides a closed magnetic circuit and at least a first main winding. At least one first conductor wound around the body along at least part of a closed circuit for one winding and at least one winding forming a second main winding or control winding And at least one second conductor wound around the body along at least a portion of the closed circuit for the winding of one or more of the main windings of the control winding It is characterized in that it is perpendicular to the winding axis of one or more windings. The purpose is to provide an orthogonal magnetic field to the body, thereby adjusting the characteristics of the magnetizable material with respect to the magnetic field of the main winding by the magnetic field of the control winding. In a preferred variant of this first embodiment, the winding axis of the main winding is parallel to or coincides with the longitudinal direction of the body, while the winding of the control winding is substantially along the magnetizable body. Therefore, the axis of the control winding is perpendicular to the longitudinal direction of the body. A second possible variant of the first embodiment is that the winding axis of the control winding is parallel to or coincides with the longitudinal direction of the body, while the winding of the main winding is along the magnetizable body. So that the axis of the main winding is perpendicular to the longitudinal direction of the body.
[0017]
This first embodiment of the apparatus comprises a third electrical conductor wound around the body along at least part of the closed circuit of at least one winding forming the third main winding, The winding axis of one or more windings of the three main windings is coincident with or parallel to the winding axis of one or more windings of the first main winding, so that the first and third It can be adapted for use as a transformer providing a transformer action between them when at least one of the main windings is excited. A second possibility for applying the first embodiment of the invention for use as a transformer is that of the body along at least part of a closed circuit of at least one winding forming a third main winding. It has one third conductor wound around and the winding axis of one or more windings of the third main winding coincides with the winding axis of one or more windings of the first control winding Or in parallel therewith, thus providing a transformer action between them when at least one of the third main winding and the control winding is energized.
[0018]
The second embodiment of the present invention comprises a magnetic induction type current or voltage regulator, both main bodies being juxtaposed, a first main body and a second main body made of a magnetizable material providing a magnetic circuit, and a first main winding At least one first conductor wound along at least a portion of a closed circuit of at least one winding forming a line and a first of at least one winding forming a second main winding or control winding. And / or at least one second conductor wound along at least a portion of the second body. The purpose is to provide an orthogonal magnetic field in the body, thereby adjusting the characteristics of the magnetizable material with respect to the magnetic field of the main winding by the magnetic field of the control winding. The main and control windings can of course be exchanged, so that a magnetic induction type current or voltage regulator is provided and the first and / or first of at least one winding forming the first main winding. Winding along at least a portion of a closed circuit of at least one first conductor wound around at least a portion of the two bodies and at least one winding forming a second main winding or control winding A winding axis of one or more windings of the main winding, the winding axis of one or more windings of the control winding for the purpose of providing an orthogonal magnetic field of the main body And thereby adjusting the characteristics of the magnetizable material with respect to the magnetic field of the main winding by the magnetic field of the control winding.
[0019]
A preferred modification of the second embodiment comprises first and second magnetic field couplers that cooperate with both bodies forming a closed magnetic circuit.
[0020]
This second embodiment of the device can be applied for use as a transformer, and consists of one third conductor wound as one winding forming the third main winding, and the third main winding. The winding axis of the winding or windings of the wire is coincident with or parallel to the winding axis of the winding or windings of the first main winding, and therefore the third main winding and the first winding When at least one of the main windings is energized, it provides a transformer action between the third main winding and the first main winding or the control winding.
[0021]
In a preferred variant of this second embodiment of the invention, the first and second bodies are tubular and thus extendable through the first and second bodies. In this variation, the magnetic field coupler comprises a conductor aperture. In a more preferred embodiment of the present invention, each magnetic field coupler comprises an air gap to facilitate the insertion of the first or second conductor. In an even more preferred embodiment, the device comprises an insulating film disposed between the end face of the tubular body and the magnetic field coupler. This is intended to insulate the contact surfaces from each other and to prevent induced eddy currents generated on the contact surfaces due to short-circuiting of the film layers. When the core is made of ferrite or compressed powder, an insulating film is not required. Furthermore, it is particularly advantageous that each tubular body of this second embodiment consists of two or more core members and that an insulating layer is provided between the core members. The tubular body of this second embodiment of the present invention may further be characterized by having a circular, square, rectangular, triangular or hexagonal cross section.
[0022]
The third embodiment of the present invention relates to a magnetic induction type current or voltage regulator, which is made of a magnetizable material and is concentric with each other, and thus has a common axis and provides a closed magnetic circuit. An outer tubular body and a second inner tubular body, at least one first conductor wound around at least one winding tubular body forming the first main winding, and a gap between both tubular bodies And at least one second conductor wound around a common axis of at least a portion of the tubular body forming the second main winding or control winding, and one or more of the main winding The winding axis of the winding is perpendicular to the winding axis of one or more windings of the control winding. Again, this objective provides an orthogonal magnetic field between the tubular bodies, thereby adjusting the properties of the magnetizable material with respect to the magnetic field of the main winding by the magnetic field of the control winding. The main winding and the control winding are also interchangeable in this third embodiment of the invention, thus providing a magnetic induction type current or voltage regulator, wherein at least one first conductor is between the tubular bodies. Winding around a common axis of at least one winding tubular body providing space and forming a first main winding, at least one second conductor forming a second main winding or control winding At least one winding is wound around both tubular bodies, and the winding axis of one or more windings of the main winding is perpendicular to the winding axis of one or more windings of the control winding.
[0023]
A preferred variant of this third embodiment of the invention consists of first and second magnetic field couplers that cooperate with the tubular body to form a closed magnetic circuit.
[0024]
This third embodiment of the device can also be applied for use as a transformer by including one third conductor wound as one winding forming the third main winding. Even in this case, the winding axis of the one or more windings of the third main winding is coincident with or parallel to the winding axis of the one or more windings of the first main winding, and therefore When at least one of the first and third main windings is excited, a transformer action is provided between them, or one or more winding axes of the third main winding are controlled windings. A line between the winding axis of one or more windings, or parallel to this, so that when at least one of the third main winding and the control winding is energized, there is a transformer between them. Provides action.
[0025]
The fourth embodiment of the present invention relates to a magnetic induction type current or voltage regulator, and in the same manner as the third embodiment of the present invention, each of the first outer layers is made of a magnetizable material and is composed of a magnetic closed circuit or an inner core. A tubular body and a second inner tubular body are provided. The device also provides an outer core attached to the outside of the first outer tubular body, and the two tubular bodies are concentric with each other, and thus the additional tubular body having a common axis, and the first main winding. At least one first conductor wound around both tubular bodies of at least one winding forming a wire, and attached to a space between the first and second tubular bodies and a second main winding or control winding And at least one second conductor wound around a common axis of at least one winding tubular body forming a wire, wherein the winding axis of one or more windings of the main winding is a control winding Is perpendicular to the winding axis of one or more windings. Again, the purpose is to provide an orthogonal magnetic field of the tubular body, thereby adjusting the properties of the magnetizable material with respect to the magnetic field of the main winding by the magnetic field of the control winding. In the same way as the second embodiment of the invention, the main winding and the control winding are interchangeable, so that a device provided with at least one conductor is provided in the space between the first and second tubular bodies And at least one second conductor wound around the common axis of the tubular body for the at least one winding forming the second main winding or control winding is the second main winding or control winding. It is wound around a tubular body for at least one winding forming a wire.
[0026]
A preferred variant of this fourth embodiment of the invention consists of first and second magnetic field couplers that cooperate with the tubular body to provide a closed magnetic circuit.
[0027]
This fourth embodiment of the device can also be applied for use as a transformer by including one third conductor wound as one winding forming the third main winding. Even in this case, there are two variations. That is, one is that the winding axis of one or more windings of the third main winding is coincident with or parallel to the winding axis of one or more windings of the first main winding, and therefore When at least one of the first and third main windings is excited, it provides a transformer action between them. One is that the winding axis of one or more windings of the third main winding is coincident with or parallel to the winding axis of one or more windings of the control winding. When at least one of the main and control windings is energized, it provides a transformer action between them.
[0028]
Of course, it is possible to carry out this fourth embodiment of the invention, in which two tubular bodies forming the inner core are attached to the outside of the tubular body forming the outer core. Thus, it is possible to provide an inner core with one tubular body and an outer core with two tubular bodies.
[0029]
In a preferred variant of the fourth embodiment of the invention, the device has an outer core consisting of several annular members, and the first and / or third main windings are each winding around each annular member. It is characterized by forming. A second possibility is that the control winding and / or the third main winding can form a respective winding around each annular member.
[0030]
The fourth embodiment is a preferred embodiment in principle.
[0031]
The device according to the invention has a number of interesting applications. Only a few examples will be described. These include the following: That is, a) an element in the frequency converter that converts the input frequency to a randomly selected output frequency, preferably intended for the operation of an asynchronous motor in the cycloconverter connection, b) a random selection of the input frequency Intended to actuate an asynchronous motor as a connector in a frequency converter that converts to a specific output frequency and to add a portion of the phase generated from a 6 to 12 pulse transformer to the phase of each motor C) As a DC / AC converter for converting a DC voltage / current into an AC voltage / current of a randomly selected output frequency, d) as in c), but three variable inductance voltage conversions of this kind. Appliances interconnected to generate a three-phase voltage with a randomly selected output frequency connected to the asynchronous machine, e) AC within the processing industry For converting voltage into DC voltage, the device is used as a magnetoresistive controlled variable transformer, the output voltage of which is magnetically coupled in parallel or in series with an external or internal core with a separate secondary winding Three or more such magnetoresistive controlled transformers are connected to known three phase rectifier connections for 6 or 12 pulse rectifier connections for the diode output stage. F) a variable inductance in series with a primary winding of a known transformer connection, used in a rectifier for converting AC voltage to DC voltage for use within the processing industry and forming a voltage connector And three or more transformers connected to a three-phase rectifier connection for a 6 or 12 pulse rectifier connection for a diode output stage, g) device A magnetic resistance controlled variable transformer is formed, the output voltage of which is magnetically controlled by a filter in parallel or in series with an external or internal core with an isolated secondary winding, preferably with an inductance formed of a variable inductance. For AC / DC or DC / AC converters used in the magnetic field of a switching power supply to reduce the size of the magnetic voltage converter to be proportional to the magnetoresistive change in the core connected to the h, high voltage distribution As an element in the adjustable voltage compensator in the network, where the device produces a linear variable inductance, i) As an element in the adjustable reactive power compensator (VAR element), the device is associated with a known filter circuit. Linear variable inductance, where at least one capacitor is included as an element and is in the form of a magnetoresistive controlled transformer The device is used as an element in a compensator connection and the capacitance or inductance of the connection is automatically combined and adjusted to the extent required to compensate for reactive power, j) DC voltage of AC voltage Also in the system for magnetoresistive controlled direct conversion to k) is in the system for magnetoresistive controlled direct conversion of DC voltage to AC voltage.
[0032]
The voltage connector has no moving parts to absorb the voltage between the generator and the load. The function of the connector is that the voltage between the generator and the load can be controlled from 0 to 100% with a small control current. The second function is to act as a pure voltage switch or as a current regulator. A further function is that a voltage curve can be formed and transformed.
[0033]
The new technology based on the present invention can be used to enhance the quality of existing diode rectifiers that require adjustment. In connection with a 12-pulse or 24-pulse rectification system, the system voltage is balanced in a simple manner while allowing 0-100% diode rectification operation to be controlled.
[0034]
The current or voltage regulator according to the invention is implemented in the form of a magnetic connector substantially free of moving parts and can be used for connection, thereby transferring electrical energy between the generator and the load. it can. The function of the magnetic connector is to enable opening and closing of the electric circuit.
[0035]
Thus, the connector acts in a different way than the transducer where the transformer principle is used to saturate the core. Current connectors control the operating voltage by putting the main core with the main winding into and out of saturation with the control winding. The connector has no noticeable transformer function or inductive coupling between the control winding and the main winding (as opposed to the transducer), i.e. no significant common magnetic flux is generated between the control winding and the main winding.
[0036]
This novel magnetic control connector technology can replace GTO in high power applications and semiconductors such as MOSFETs or IGBTs in other applications, but formed by no-load current in the manufacture of the main winding Aside from being limited to applications that can withstand stray currents. As mentioned in the introduction, new converters that convert AC power with a given frequency into AC power with different selected output frequencies are particularly suitable for implementing frequency converters. An intermediate DC connection is not required in this case.
[0037]
As mentioned at the outset, the device according to the invention can be used in connection with a frequency converter. For example, based on the cycloconverter principle, but possible by a frequency converter based on a 12-pulse bridge converter, or by directly converting a DC voltage to a variable frequency AC voltage.
[0038]
The principle of the device according to the invention in which a variable reluctance is used for the magnetizable body or main core is that the magnetizing current in the main winding wound around the main winding is determined by the magnetic flux resistance based on Faraday's law. Based on the fact that it is limited. The magnetic flux that must be established to generate the counter electromotive voltage depends on the magnetic flux resistance in the magnetic core. The magnitude of the magnetizing current is determined by the amount of magnetic flux that must be established to balance the applied voltage.
[0039]
The magnetic flux resistance in the coil whose core is air is on the order of 1.000 to 900.000 times that of the winding wound around the core of the ferromagnetic material. In the case of low flux resistance (iron core), a small current is required to establish the magnetic flux necessary to generate a backing voltage for the applied voltage based on Faraday's law. In the case of high flux resistance (air core), a large current is required to establish the magnetic flux required to generate the same induced blocking voltage.
[0040]
By controlling the magnetic flux resistance, the magnetizing current or the load current in the circuit can be adjusted. In order to adjust the magnetic flux resistance, according to the invention, a control magnetic flux is used in which the saturation of the main core is orthogonal to the magnetic flux generated by the main winding. As described above, the above principle is the basis of the present invention and relates to a magnetic induction type current or voltage regulator (connector) and a magnetic induction type converter device.
[0041]
It will be appreciated that both connectors and converters can be suitably produced by production equipment using toroidal cores. From a technical point of view, the converter can be produced by winding a magnetic material such as electroplating around a suitably designed cylindrical core, or using compressed powder or ferrite for high frequency applications. Of course, there is also an advantage of producing a ferrite core or a compacted powder core based on the application instructions.
[0042]
The invention will now be described in more detail with reference to the accompanying drawings.
[0043]
The principle of the present invention will now be described with reference to FIGS. 1a and 1b.
[0044]
Throughout the description, the arrows for magnetic and magnetic flux substantially indicate their direction within the electrical material. The arrows are drawn outside the figure for clarity.
[0045]
FIG. 1a shows a device consisting of a body 1 of magnetizable material forming a closed magnetic circuit. This magnetizable body or core 1 is annular or other suitable shape. The direction of the magnetic field H1 (corresponding to the direction of the magnetic flux density B1) generated when the first main winding 2 is wound around the main body 1 and the main winding 2 is excited follows the magnetic circuit. Yes. The main winding 2 corresponds to a winding in a normal transformer. In an embodiment, the device includes a second main winding 3, which is wound around the magnetizable body 1 and thereby substantially along the body 1 (ie H1). , Parallel to B1) to provide an extended magnetic field. The apparatus finally includes a third main winding 4 in the preferred embodiment of the invention that extends inwardly along the magnetic body 1. The magnetic field H2 (and hence the magnetic flux density B2) formed when the third main winding 4 is excited is perpendicular to the direction of the magnetic field in the first and second main windings (directions H1, B1). . The present invention also includes a fourth main winding 5 wound around the leg of the body 1. When the fourth main winding 5 is excited, it generates a magnetic field in a direction perpendicular to the first (H1) magnetic field and the second and third main windings (H2) (FIG. 3). This necessitates the use of a closed magnetic circuit for the magnetic field generated by the fourth main winding. This circuit is not shown in the figure. This is because the figure is only intended to represent the relative position of the windings.
[0046]
However, in the topology considered preferable in this description, the windings (turns) in the main winding follow the magnetic field direction from the control magnetic field, and the windings in the control winding follow the magnetic field direction with respect to the main magnetic field. .
[0047]
1b to 1g show the definition of the shaft and the direction of the different windings and magnetic bodies. With regard to the windings, the perpendicular to the surface limited by each winding (turn) will be called the axis. The main winding 2 has an axis A2, the main winding 3 has an axis A3, and the control winding 4 has an axis A4.
[0048]
With respect to the magnetizable body, the longitudinal direction changes in relation to the shape. If the main body is long, the longitudinal direction A1 corresponds to the long axis of the main body. If the magnetized body is square as shown in FIG. 1a, the longitudinal direction A1 can be defined by each leg of the square. If the main body is tubular, the longitudinal direction A1 becomes the tube axis, and in the annular main body, the longitudinal direction A1 follows the periphery of the ring.
[0049]
The invention is based on the possibility of changing the characteristics of the magnetizable body 1 in relation to the first magnetic field by changing a second magnetic field perpendicular to the first magnetic field. Thus, for example, the magnetic field H1 can be defined as an actuation magnetic field and is controlled by the characteristics of the body 1 (and hence the characteristics of the actuation magnetic field H1) by the magnetic field H2 (hereinafter referred to as the control magnetic field H2). This will be described in detail next.
[0050]
The magnetizing current in the conductor housed by the ferromagnetic material is limited by the magnetoresistance based on Faraday's law. The magnetic flux that must be established to generate the counter electromotive force depends on the reluctance of the magnetic material containing the conductor.
[0051]
The range of the magnetizing current depends on the amount of magnetic flux that must be established in order to balance the applied voltage. In general, the following stationary equation applies to sine waves:
1) Magnetic flux:

E = Applied voltage
ω = angular frequency
N = number of turns
Here, the magnetic flux Φ through the magnetic material is determined by the voltage E. The current required to establish the required magnetic flux is determined by the following equation:
2) Current:

3) Magnetic resistance (magnetic flux resistance)

1J = magnetic path length
μr = relative permeability
μ0 = permeability in vacuum
Aj = sectional area of magnetic path
[0052]
If there is a low reluctance here (iron container), the above equation 2) is required to establish the magnetic flux required by the small current, and the applied voltage overlays the connector. On the other hand, in the case of high reluctance (air), a large current is required to establish the required magnetic flux. Thus, in this case, the current is limited by the voltage across the load and the voltage induced in the connector. The difference between the magnetic resistance in air and the magnetic resistance in the magnetic material will be in the range of 1.000 to 900.000.
[0053]
The magnetic induction or magnetic flux in the magnetic material is determined by the relative permeability and magnetic flux density of the material. The magnetic field strength is generated by a current in a winding placed around or in the material.
[0054]
For the system to be evaluated, the following formula applies:
Magnetic field strength

H￣ = magnetic field strength
s = integral path
I = current in winding
N = number of turns
Magnetic flux density or induction

H￣ = magnetic field strength
[0055]
The ratio between the magnetic induction and the magnetic field strength is non-linear, and as a result, when the magnetic field strength increases above a certain limit, the magnetic field of the ferromagnetic material is saturated due to the fact that the magnetic domain of the ferromagnetic material is saturated. The density will not increase. Thus, in order to control the saturation in the magnetized material, a control magnetic field H2 is provided perpendicular to the working magnetic field H1 in the magnetic material, while the magnetic coupling between the two magnetic fields is blocked, whereby a transformer coupling or inductive junction It is desirable to prevent this. Transformer coupling means that two windings “share” the magnetic field, so that changes in the magnetic field from one winding result in changes in the magnetic field in the other winding.
[0056]
In order for the increasing H to prevent saturation due to transformer coupling, the magnetic fluxes have a common path and will be added together. If the magnetic fluxes are orthogonal, the magnetic fluxes are not added to each other. For example, by providing the magnetic material in the form of a tube, the main winding or the winding in which the working current flows is arranged inside and wound in the longitudinal direction of the tube, and the winding in which the control winding or the control current flows is provided. By winding the wire around the tube, the desired effect is achieved. Depending on the dimensions of the tube, a small area for the control flux and a large area for the working flux are thereby achieved.
[0057]
In the above embodiment, the working magnetic flux flows along the circumference of the tube, and a closed magnetic circuit is formed. On the other hand, the control flux flows in the longitudinal direction of the tube, the two tubes are arranged in parallel, and the magnetic material connects the control flux between the two tubes, or the first tube is around the second tube. Are arranged in a closed magnetic circuit, so that the control winding is located between the two tubes and the end faces of the tubes are magnetically interconnected, so that the control flux A closed path is obtained. These solutions will be explained in more detail later.
[0058]
The member that provides the magnetic coupling between the tubes or the cores is hereinafter referred to as a magnetic connector or magnetic field coupling.
[0059]
The total magnetic flux in the material is

Given by.
[0060]
The magnetic flux density B consists of the vector sum of B1 and B2 (FIG. 4d). B 1 is generated by the current I 1 in the first main winding 2, and B 1 has a tangential direction to the electrical conductor in the main winding 2. The main winding 2 has N1 turns and is wound around the magnetizable body 1. B2 is generated by the current I2 in the control winding 4 having N2 turns, and the control winding 4 is wound around the main body 1. B 2 is tangential to the conductor in the control winding 4.
[0061]
Since the windings 2 and 4 are arranged at 90 ° to each other, B1 and B2 are arranged at a right angle. Within the magnetizable body 1, B1 is directed across and B2 is oriented longitudinally. This point is particularly shown in FIGS.
[0062]

The relative permeability is higher in the working magnetic field (H1) than in the direction of the control magnetic field (H2), ie the magnetic material in the magnetizable body 1 is anisotropic, of course, this is the concept of the invention It is not considered to be limited with respect to.
[0063]
The vector sum of the magnetic fields H1 and H2 will determine the total magnetic field in the body 1, and therefore the condition of the body 1 for saturation will determine the magnetizing current and voltage, which is connected to the winding 2 Divided between the load and the connector. Since the magnetic flux sources B1 and B2 are arranged orthogonal to each other, neither magnetic field can be decomposed into the other magnetic field. This means that B1 is not a function of B2, and B2 is not a function of B1. However, B, which is the vector sum of B1 and B2, is affected by the respective ranges of both.
[0064]
B2 is a vector generated by the control current. The section A2 for the B2 vector is the transverse section of the magnetic body 1. See Figure 4c. This is a small surface limited by the thickness of the magnetizable body 1 and in the case of an annular body is given by the surface sector between the inner and outer diameters of the body 1. On the other hand, the cross section A1 (see FIGS. 4a and b) for the B1 magnetic field is given by the length of the magnetic core and the rating of the applied voltage. This surface is 5 to 10 times larger than the surface of the control magnetic flux density B2, but this does not take into account limiting the present invention.
[0065]
When B2 is at the saturation level, the change in B1 does not become the change in B. This allows B1 to control the level of material saturation.
[0066]
The inductance of the control winding 4 (with N2 turns) can be rated to a small value suitable for regulator pulse control, i.e. it can provide a fast response (on the order of milliseconds).
[0067]

N2 = number of turns of control winding
A2 = area of control magnetic flux density B2
l2 = length of magnetic flux path of control magnetic flux
[0068]
A simplified mathematical representation is shown below for the present invention and its applications based on Maxwell's equations.
[0069]
For simple calculation of magnetic fields in power technology, Maxwell's equations are used in integral form.
[0070]
In the type of device to be analyzed here (the invention also has some extension), the magnetic field has a low frequency.
[0071]
Therefore, the displacement current can be ignored compared to the current density.
[0072]
Maxwell's equations

Is

To be simplified.
[0073]
The integral form can be found in the Talk's theorem:

Represents the solution for the system in FIG. 4, where the main winding 2 establishes the H1 field. Here, the focus is on the principle, the calculation is performed in the case of concentrated winding, and accurate calculation is not performed.
[0074]
The integration path coincides with the magnetic field direction and the average magnetic path length 11 is selected within the magnetizable body 1. The solution of the integral equation is

It becomes. This is also known as magnetomotive force MMK.

[0075]
A control winding 4 is established corresponding to the MMK generated by the current I2:

[0076]
The magnetization of the material under the influence of the H magnetic field generated from the source windings 2 and 4 is represented by the magnetic flux density B. For main winding 2:

For control winding 4:

[0077]
The permeability in the horizontal direction is about 10 to 20 times smaller than that in the vertical direction. The permeability in vacuum is:

[0078]
The capacity to conduct the magnetic field in iron is μ _r And the size of μ is 1000 to 100.000 for iron and up to 900.000 for the new Metglas material.
[0079]
By combining equations 11) and 15), for the main winding 2, the following equation is obtained:

[0080]
The magnetic flux in the magnetizable body 1 from the main winding 2 is given by:

[0081]
Assuming that the magnetic flux is constant across the core cross section:

[0082]
Now confirming the equation for the magnetic flux resistance Rm or magnetoresistance given under 3):

[0083]
Similarly, examining the magnetic flux and reluctance for the control winding 4:

[0084]
The present invention is based on the physical fact that the difference in magnetic field strength with its source in the current in the conductor is represented by vector rotation with respect to the H field. The vector rotation of H is to say something about the differential or magnetic field change of the H magnetic field that crosses the magnetic field direction of H. In this case, the magnetic field is calculated based on the fact that the plane perpendicular to the differential magnetic field loop has the same direction as the current. This means that the magnetic fields from the current-carrying conductors forming the windings perpendicular to each other are also orthogonal. It is true that magnetic fields that are perpendicular to each other are important with respect to the orientation of the domains in the material.
[0085]
Before examining this point more closely, we introduce self-inductance, which plays a major role in the application of new magnetically controlled power elements.
[0086]
According to Maxwell's equation, a time-varying magnetic field induces a time-dependent electric field,

Is represented by
[0087]
The left side of the integral represents a potential formula in the integral form. The source of the magnetic field change is the voltage from the generator, and when the winding has N turns, it can be expressed by Faraday's law, and the magnetic flux passes through all turns. See FIG.

λ (Wb) represents the number of turns of the magnetic flux and is the sum of the magnetic fluxes passing through each number of turns in the winding. Considering the intermittent generator G in FIG. 5b after the magnetic field has been established, the change in flux source is the current in the circuit and comes from existing circuit technology. See Figure 5a.

[0088]
From Equation 21,

Is obtained.
[0089]
When L is constant, the combination of Equation 26 and Equation 27:

Is obtained.
[0090]
The solution of Equation 29 is:

It is.
[0091]
From Equation 28 we derive that C is 0 and:

Is derived.
[0092]
This represents self-induction for winding N (or main winding 2 in this case). Self-induction is equal to the ratio between the number of magnetic flux turns established by the current in the winding (coil) and the current in the winding (coil).
[0093]
Self-induction in the winding is almost straight as long as the magnetizable body or core is not saturated. However, the change in permeability in the material of the magnetizable body is changed by the control magnetic field (ie by the magnetic field H2 established by the control winding 4) to change the self-inductance by changing the transverse domain magnetization.
[0094]
Combining Equation 21 and Equation 31,

Get.
[0095]
AC resistance or reactance in an electric circuit with self-inductance is

Obtained by.
[0096]
By magnetizing the domains in the magnetizable body in the transverse direction, the longitudinal magnetoresistance changes. What happens to the domains during the influence of different magnetic fields is not described in detail here. Here, considering a typical commercial electroplating with a silicon content of approximately 3%, this description does not seek a description of the phenomenon relating to the met-glass material, but of course this limits the invention. It is not a consideration. This is because magnetic materials with an amorphous structure play an important role in certain applications of the present invention.
[0097]
In transformers, a small amount of energy is stored in the magnetic stray field and in the core, but the stored energy does not form a direct part during the conversion of energy, and consequently the energy conversion is electrical. It uses a closed core that has a high permeability that does not occur in terms of occurring in the mechanical system, ie, electrical energy is converted to mechanical energy, but energy is not converted via magnetic flux through the transformer. In an inductance coil or choke with a gap, the magnetoresistance in the gap is dominant compared to the magnetoresistance in the core, and almost all the energy is stored in the gap.
[0098]
In the device according to the invention, “virtual” voids are generated by saturation phenomena in the domains. In this case, energy storage occurs in a distributed air gap consisting of all cores. Consider an actual energy storage system that is lossless and therefore any loss is represented by external elements.
[0099]
The description of energy used here is based on the law of conservation of energy.
[0100]
The first law of the lossless electromagnetic system described above is
dWelin = dWfld 34)
And see FIG.
Where dWelin = differential electrical energy supply
dWfld = differential change in magnetic storage energy
[0101]
From Equation 26:

Is obtained.
[0102]
Here, the inductance is variable through an orthogonal magnetic field or control magnetic field H2, and Equation 31 is substituted into Equation 26,

Get.
[0103]
The action in the system is

Therefore,

Get.
[0104]
For a system with a core that can change the reluctance and only the main winding, substituting Equation 37 into Equation 35,

Get.
[0105]
In the device according to the invention, L varies as a function of μr, and then the relative permeability in the magnetizable body or core 1 is a function of the control current I 2 in the control winding 4.
[0106]
When L is constant, i.e., when I2 is constant, dL is equal to 0, so the part ixdL can be ignored, so the magnetic field energy is

Given by.
[0107]
When L is changed by I2, the magnetic field energy will change as a result of the change value of L, so that the current I also changes because it is related to the magnetic field value by the number of magnetic flux turns λ. Since i and λ are variable, they are functions of each other, while there is a non-linear function, and mathematics beyond the scope of the description of the present invention is required. Therefore, no solution is obtained here.
[0108]
However, the magnetic field energy and energy distribution can be controlled by μr, and a conclusion can be drawn how the effect of the energy stored in the magnetic field increases or decreases. When the magnetic field energy is reduced, the excess will be returned to the generator. Alternatively, if an extra winding (for example, the winding 3 in FIG. 1) is provided in the same winding window as the first main winding 2 and the same winding axis, the first winding 2 to the second main winding 3 are provided. A transforming conversion of energy is provided.
[0109]
This is shown in FIG. 7, where a change in λ is a change in the magnetic field Wflt which is Wflt (λ0, i0) at the origin. The change is expected to be very small here, and i is nearly constant during the change of λ. Therefore, the following can be said when looking at the variable inductance.
[0110]
What happens is shown in FIGS.
[0111]
FIG. 8 shows the magnetization curve for all materials of the magnetizable body 1 and the domain change under the influence of the H1 magnetic field from the main winding 2.
[0112]
FIG. 9 shows the magnetization curve for all materials of the magnetizable body 1 and the domain change under the influence of the H2 magnetic field in the direction from the control winding 4.
[0113]
10a and 10b show the magnetic flux density B1 (the magnetic field H1 is established by the working current) and B2 (corresponding to the control current). The ellipse indicates the saturation limit of the B magnetic field. That is, when the B magnetic field reaches the limit, this causes the material of the magnetizable body 1 to reach saturation. The shape of the elliptical axis is given by the magnetic path length and permeability of the two magnetic fields B1 (H1) and B2 (H2) in the core material of the magnetizable body 1.
[0114]
By drawing an axis in FIG. 10, the MMK distribution or the H magnetic field distribution is represented, and the magnetomotive force due to the two currents I and I2 can be confirmed from the figure.
[0115]
Reference is again made to FIGS. Due to the partial magnetization of the domain by the control magnetic field B2 (H2), the additional magnetic field B1 (H1) from the main winding 2 is added to the control magnetic field B2 (H2) in a vector manner, and the domain is further magnetized, resulting in As a result, the inductance of the main winding 2 starts from the base given by the state of the domain under the influence of the control magnetic field B2 (H2).
[0116]
This linearly changes the domain magnetization, inductance L and AC resistance XL as a function of the control magnetic field B2.
[0117]
Various embodiments of the device according to the invention will now be described with reference to the remaining figures.
[0118]
FIG. 11 schematically shows a second embodiment of the present invention.
[0119]
FIG. 12 shows the same embodiment of the magnetic influence connector according to the invention, FIG. 12a shows the assembled connector and FIG. 12b shows the connector viewed from the end.
[0120]
13 is a cross-sectional view taken along line II in FIG. 12b.
[0121]
As shown, the magnetizable body 1 consists of two parallel tubes 6 and 7 made in particular from a magnetizable material. An electrically insulated conductor 8 (FIGS. 12a and 13) is continuously passed through a path passing through the first tube 6 and the second tube 7 having N turns. Where N = 1,. . . The first main winding 2 is formed by r, and the conductor 8 extends in the opposing direction passing through the two tubes 6 and 7 as clearly shown in FIG. It only shows that the conductor 8 is extended through the first tube 6 and the second tube 7 twice, but the conductor 8 is only once in each tube or several times (the number of turns). It is self-evident that N can be varied from 0 to r), and can be extended by passage, thus creating a magnetic field H1 in the parallel tubes 6 and 7 when the conductor is excited. can do. A combination of the control winding 4 and the magnetizing winding 4 ′ made of the conductor 9 is wound around the first tube and the second tube (6 and 7 respectively), and the direction of the magnetic field H2 (B2) is When the winding 4 is excited, the direction of the magnetic field H2 (B2) generated in both the tubes is the opposite direction as indicated by the arrow with respect to the magnetic field B2 (H2) in FIG. Made in the way. The magnetic field couplers 10 and 11 are attached to both ends of the respective tubes 6 and 7 so that both the tubes are interconnected in the magnetic field direction to form a loop. The conductor 8 is adapted to pass a load current I1 (FIG. 12a). The length and diameter of the tubes 6, 7 are determined based on the power and the voltage that must be connected to it. The number of turns N1 of the main winding 2 is determined by the reverse blocking ability of the voltage and the cross-sectional area in the range of the working magnetic flux φ2. The number N2 of turns of the control winding 4 is determined by the magnetic field required for saturation of the magnetizable body 1 consisting of the tubes 6, 7 and the magnetic field couplers 10, 11.
[0122]
FIG. 14 shows a special design of the main winding 2 in the device according to the invention. In fact, the solution of FIG. 14 differs from that shown in FIGS. 12 and 13 in that instead of a single insulated conductor 8 passed through both tubes 6 and 7, two separate facings are directed. It is a fact that the used conductors, so-called first conductor 8 and second conductor 8 'are used, thereby achieving a voltage converter for a magnetic induction type device according to the invention. This will be described in detail next. This design is basically similar to that shown in FIGS. The magnetizable body 1 consists of two parallel tubes 6 and 7. The electrically insulated first conductor 8 continuously passes through a path passing through the first tube 6 and the second tube 7 having the number of turns N1. Where N1 = 1,. . . r, the primary conductor 8 extends through the two tubes 6 and 7 in the opposite direction. An electrically insulated second conductor 8 ′ continuously passes through a path passing through the first tube 6 and the second tube 7 having the number of turns N1 ′. Here, N1 ′ = 1,. . . r, the second conductor 8 ′ extends in the opposite direction to the first conductor 8 through the two tubes 6 and 7. At least one combined control winding 4 and magnetized winding 4 'are wound around each of the first tube 6 and the second tube 7, so that the magnetic field directions generated on the tube are directed in opposite directions. . As far as the embodiment according to FIGS. 11, 12 and 13 is concerned, the magnetic field couplers 10, 11 have their respective tubes 6 and 7 looped together, thereby interconnecting them in the direction of the magnetic field in which the magnetizable body 1 is formed. It is provided at the end of the tube (6, 7). For the sake of simplicity, only a single path through both tubes 6 and 7 is shown for first conductor 8 and second conductor 8 ', but both first conductor 8 and second conductor 8' It can be readily seen that tubes 6 and 7 have been passed with N1 and N1 ′ turns, respectively. The length and diameter of the tubes 6 and 7 are determined based on the power and voltage to be converted. In a transformer having a conversion (transformation) ratio (N1: N1 ′) equal to 10: 1, in practice, ten conductors are used as the first conductor 8, and only one conductor is the second conductor. Used for 8 '.
[0123]
An embodiment of the magnetic field coupler 10 and / or 11 is shown in FIG. A magnetic field coupler 10, 11 made of a magnetically conductive material is shown, where two preferred circular apertures 12 (see, eg, FIG. 13) for the conductor 8 of the main winding 2 are in the connectors 10, 11. Machined to magnetic material. In addition, a gap 13 is provided to interrupt the magnetic field path of the conductor 8. The end face 14 is a coupling face for the magnetic flux H2 from the control winding 4 composed of the conductors 9 and 9 '(FIG. 13).
[0124]
FIG. 16 shows a thin insulating film 15 disposed between the end faces of the tubes 6 and 7 and the magnetic field couplers 10 and 11 of the preferred embodiment of the present invention.
[0125]
17 and 18 show another embodiment which can be substituted for the magnetic field couplers 10 and 11.
[0126]
FIGS. 19-32 show various embodiments of the core 16 of the embodiment shown in FIGS. 12, 13 and 14, with the cores forming the main parts of the tubes 6 and 7 together with the magnetic field couplers 10 and 11. The magnetizable main body 1 is formed.
[0127]
FIG. 19 shows the longitudinally divided cylindrical core member 16 with one or more layers 17 of insulating material disposed between the two core halves 16 ′ and 16 ″.
[0128]
FIG. 20 shows a rectangular core member 16, and FIG. 21 shows an embodiment in which the core member 16 is divided into two partial members on its lateral surface. In the embodiment shown in FIG. 21, one or more layers of insulating material 17 are disposed between the core halves 16, 16 '. FIG. 22 shows a further modification in which a partial member is provided at each corner.
[0129]
23, 24 and 25 show a rectangular shape. Figures 26, 27 and 28 show the same triangular shape. 29 and 30 show an oval shape, and finally FIGS. 31 and 32 show a hexagonal shape. In Fig. 31, the hexagonal shape consists of six equal faces 18, and in Fig. 32 the hexagonal shape consists of two members 16 'and 16 ". Reference numeral 17 denotes a thin insulating film.
[0130]
FIGS. 33 and 34 show magnetic field couplers 10, 11 that can be used as control magnetic field couplers between rectangular and rectangular main cores 16 (shown in FIGS. 20-21 and 23-25, respectively). The magnetic field coupler is composed of three members 10 ′, 10 ″ and 19.
[0131]
FIG. 34 shows an embodiment of the core member or main core 16, and the end face 14 or the connection face of the control magnetic flux is perpendicular to the axis of the core member 16.
[0132]
FIG. 35 shows a second embodiment of the core member 16 in which the end face 14 of the control magnetic flux forms an angle α with the axis of the core member 16.
[0133]
36-38 show various designs of the magnetic field couplers 10, 11, and the connection surface 14 ′ of the magnetic field couplers 10, 11 is based on the fact that the end surface 14 is the same angle with respect to the core member 16.
[0134]
FIG. 36 shows magnetic field couplers 10 and 11, whose different hole shapes 12 are indicated for the main winding 2 based on the shape of the core member 16 (circular, triangular, etc.).
[0135]
In FIG. 37, the magnetic field couplers 10 and 11 are flat. This is adapted to be used in conjunction with a core member 16 with a right end face 14.
[0136]
In FIG. 38, the angle α ′ is indicated with respect to the magnetic field coupler 10, 11, and the angle α is applied to the core member (FIG. 35), so that the end face 14 and the connecting face 14 ′ coincide.
[0137]
In FIG. 39, the embodiment of the present invention shows an assembly of the magnetic connectors 10 and 11 and the core member 16. FIG. 39b shows the same embodiment as seen from the side.
[0138]
Although only each combination of magnetic field coupler and core member has been described to illustrate the present invention, other combinations are entirely possible, as will be apparent to those skilled in the art, and thus the present invention. Enter into the concept of.
[0139]
It is also possible to switch the positions of the control winding and the main winding.
[0140]
40 and 41 are a sectional view and a plan view, respectively, of a third embodiment of the magnetic induction type voltage connector device. This device (see FIG. 40b) consists of a magnetizable body 1 consisting of an outer tube 20 and an inner tube 21 (or core members 16, 16 '). Both tubes are concentric and made of a magnetizable material and have a gap 22 between the inner wall of the outer tube 20 and the outer wall of the inner tube 21. The magnetic field couplers 10 and 11 between the tube 20 and the tube 21 are attached to their respective ends (FIG. 40a). A spacer 23 (FIG. 40a) is provided in the gap 22 to keep both tubes 20, 21 concentric. A combined control / magnetization winding 4 comprising an electrical conductor 9 is wound around the inner tube 21 and disposed in the gap 22. Therefore, the winding axis A2 of the control winding coincides with the axis A1 of both tubes 20 and 21. The current supply winding or the main winding 2 composed of the conductor 8 passes through the inner pipe 21 and passes along the outside of the outer pipe 20 N1 times where N1 = 1,. . The composite control / magnetization winding 4 co-operating with the main winding 2 or the current supply conductor 8 provides a voltage connector that is easily constructed but effectively magnetically affected. This embodiment of the device can also be modified in such a way that both tubes 20, 21 have a square, rectangular, triangular, etc. cross section instead of a circular cross section.
[0141]
The main winding can also be wound around the inner tube 21, in which case the axis A2 of the main winding coincides with the axis A1 of both tubes, while the control winding is inward of the tube 21 and the tube 20 Wound around both tubes outside.
[0142]
42-44 show various embodiments of the magnetic field couplers 10,11. It is particularly suitable for the latter design of the present invention, ie the one described with respect to FIGS.
[0143]
42a shows a cross section of the magnetic field coupler 10, 11 and FIG. 42b shows its plane, the contact surface 14 'being at an angle with respect to the axis of both tubes 20, 21 (core member 16), the inner tube 21 Obviously, the outer tube 20 is at the same angle with respect to the contact surface 14.
[0144]
43 and 44 show another modification of the magnetic field couplers 10 and 11, in which the contact surface 14 'of the control magnetic field H2 (B2) is perpendicular to the main axis of the core member 16 (both tubes 20, 21). Yes. FIG. 43 shows hollow semi-annular magnetic field couplers 10, 11 having a hollow semi-circular cross section, while FIG. 44 shows an annular magnetic field coupler having a rectangular cross-section.
[0145]
A variation of the device shown in FIGS. 40 and 41 is shown in FIG. 45, where FIG. 45a shows the device viewed from the side, while FIG. 45b shows the view from above. The only difference from the voltage connector of FIGS. 40 to 41 is that the second main winding 3 is wound around the same course as the main winding 2. This provides a voltage converter that can be easily configured and is effectively magnetically affected.
[0146]
46 and 47 are a sectional view and a plan view of a fourth embodiment of a voltage connector having a concentric tube.
[0147]
46 and 47 show a voltage connector that acts as a voltage converter with a coupling core. An inner magnetoresistance control core 24 is disposed in the outer core 25 around which the main winding 2 is wound. The inner magnetoresistive control core 24 has the same structure as described above under the description of FIGS. 40 and 41 with the only difference being that there is no main winding 2 around the core 24. The only difference is that the control winding 4 is disposed in the gap 22 between the inner member 21 and the outer member forming the inner magnetoresistance control core 24. As a result, only the core 24 is magnetically resistance-controlled under the influence of the control magnetic field H2 (B2) from the current in the control winding 4.
[0148]
The main winding 2 in FIGS. 46 and 47 is a winding that wraps around both the core 24 and the core 25.
[0149]
In accordance with the present invention, the mode of operation of the magnetoresistive control voltage connector or converter described with respect to FIGS. 46 and 47 will now be described.
[0150]
Reference is also made to FIG. 55 showing the principle of connection. FIG. 65 is a simplified equivalent circuit diagram of the magnetoresistive model, Rmh is a variable magnetoresistor for controlling the magnetic flux between the windings 2 and 3, and FIG. Shows an equivalent circuit with a variable inductance connection.
[0151]
The alternating voltage V1 applied to the winding 2 establishes a magnetizing current I1 in the winding 2. This is generated by the magnetic flux φ1 + φ1 ′ in the cores 24 and 25, which is necessary to be established to provide the blocking voltage generated in the winding 2 based on Faraday's law. When the control current is not in the magnetoresistive control core 24, the magnetic flux is split between the cores 24 and 25 based on the magnetic resistance in the respective cores 24 and 25.
[0152]
In order to transfer energy from one winding to another, the inner magnetoresistive control core 24 must be supplied with a control current I2.
[0153]
By supplying the control current I2 in the positive half cycle of the AC voltage V1 in the winding 2, a half cycle voltage is obtained in the winding 2. Since energy is converted by magnetic flux displacement between the magnetoresistive control core 24 and the outer (second) core 25, the magnetoresistive control core 24 is essentially controlled by the control current I2 during the period during which it is controlled during saturation. Affected, one acting magnetic flux passes through the second outer core 25 and interacts with the primary winding 2 during energy transfer.
[0154]
When the magnetoresistive control core 24 is saturated by resetting the control magnetic flux B2 (H2) orthogonal to the working magnetic flux B1 (H1), the magnetic flux from the primary side is again divided between the cores 24 and 25, and The load connected to the secondary winding 3 has a low reluctance, so only a high inductance and a small coupling between the primary (VI) and secondary (V3) voltages are seen. Although a voltage is generated in the secondary winding 3, most of the voltage (V1) from the primary winding 2 overlays Lk considering the magnitude of Lk compared to the magnetizing impedance Lm. The magnetic flux from the primary winding 2 essentially passes through the smallest magnetic resistance and has the shortest magnetic path (FIG. 65b).
[0155]
The outer core 25 can be expected to be controllable, and the fourth main winding is wound around the inner controllable core 24. This allows the voltage between the cores 24 and 25 to be controlled as needed.
[0156]
FIG. 48 shows a further modification of the fourth embodiment of the magnetically affected voltage connector or voltage converter according to the invention, in which the magnetizable body 1 has a control magnetic flux B2 (H2) without a separate magnetic field coupler. Designed to be directly connected to the main core 16.
[0157]
FIG. 48 shows the voltage connector in an annular form when viewed from the side. This voltage connector comprises two core members 16 and 16 ′, a main winding 2 and a control winding 4.
[0158]
FIG. 49 shows a voltage connector according to the present invention with an extra main winding 3 that provides the capability of voltage conversion.
[0159]
FIG. 50 shows the apparatus of FIG. 48 in section taken along lines VI-VI in FIG. 48, and FIG. 51 shows the section seen in lines V-V. In FIG. 50, the circular aperture 12 is shown for arranging the control winding 4.
[0160]
FIG. 51 shows the additional aperture 26 for passing through the wiring.
[0161]
52 and 53 show a core structure without windings, and the core 16 is designed to not require an extra magnetic field coupler for the control field. The core 16 has two core members 16, 16 ′ and an aperture 12 for the control winding 4. This design is intended for magnetic materials using sintered or compression mold materials. In this case, it is possible to insert a closed magnetic path into the topology, so that the separate connector required so far for the foil wound core forms the actual core part and becomes a productive part of the structure. Become. The core shown in FIGS. 52 and 53, which forms a closed magnetic circuit without a separate magnetic field coupler, is illustrated even if the body 1 is applied to the first embodiment of the present invention (particularly FIGS. 1 and 2). Can be used in all embodiments of the present invention.
[0162]
FIG. 54 shows a magnetically affected voltage converter device, where the device has an inner control core 24 consisting of an outer tube 20 and an inner tube 21. Both tubes are made of a magnetizable material that is concentric and has a gap 22 between the inner wall of the outer tube 20 and the outer wall of the inner tube 21. A spacer 23 is inserted into the gap between the inner wall of the outer tube 20 and the outer wall of the inner tube 21. Magnetic field couplers 10 and 11 are mounted between the tubes 20 and 21 at their respective ends. The composite control magnetization winding 4 is wound around the inner tube 21 and disposed in the gap 22. This device further comprises an outer second core 25 with a winding consisting of a plurality of ring core coils 25 ', 25 ", 25'", etc., arranged outside the control core 24. Each ring. The core coils 25 ', 25 ", 25'" etc. consist of a ring of magnetizable material wound around by the respective main or second winding 3 for the sake of clarity only. Only one is shown. A first main winding or primary winding 2 connects the inner pipe 21 in the control core 24, and N1 = 1,. . . It passes along the outside of the outer core 25 of N1 times which is r.
[0163]
It is also conceivable to place a second core device in the control winding 24, in which case the primary winding 2 passes through the ring core 25 and along the outside of the control core 24.
[0164]
FIG. 55 is a schematic diagram of a second embodiment of a magnetically affected voltage regulator according to the present invention comprising a first magnetoresistive control core 24 and a second core, each composed of a magnetizable material and closed. Designed to form a magnetic circuit, the cores are juxtaposed. At least one first conductor 8 is wound on the main winding 2 around both the first and second core cross-sectional profiles along at least part of the closed circuit. At least one second conductor 9 is mounted as a winding 4 in the magnetoresistive control core 24 in a form essentially corresponding to a closed circuit. Additionally, at least one third conductor 27 is wound around at least part of the closed circuit around the cross-sectional shape of the second core. The magnetic field directions of the winding 2 of the first conductor and the winding of the second conductor 9 are orthogonal. With this solution, the first conductor 8 and the third conductor 27 form the primary winding 2 and the secondary winding 3, respectively.
[0165]
FIG. 56 shows a proposal of an electro-mechanical schematic symbol for a voltage connector according to the present invention. FIG. 57 shows a schematic block symbol proposal for a voltage connector.
[0166]
FIG. 58 shows a magnetic circuit not including the control winding 4 and the control magnetic flux B2 (H2).
[0167]
59 and 60 show a proposal of an electro-mechanical schematic symbol for a voltage converter in which the magnetic resistance of the control core 24 is shifted between the fixed core 25 and the second core 24 with variable reluctance. (See, for example, FIG. 55).
[0168]
Of course, the two cores are not limited to having variable magnetoresistance. The fact that the magnetic flux can be shifted between two cores in the same winding can be used to make a magnetic switch that turns the voltage on and off independent of the course of magnetization in the main core. This means that a switch having the same function as the GTO can be made except that the desired switch time can be selected at any time.
[0169]
The device according to the invention can be used for a number of different connections and examples of applications that may be particularly suitable will now be described.
[0170]
FIG. 61 illustrates the use of the present invention in an AC circuit for controlling the voltage on a load RL that is a light source, heat source or other load.
[0171]
FIG. 62 illustrates the use of the present invention in a three-phase system, where such a voltage connector for each phase connected to the diode bridge is used for linear adjustment of the output voltage from the diode bridge.
[0172]
FIG. 63 illustrates use as a variable choke in a DC-DC converter.
[0173]
FIG. 64 shows use with a capacitor as a variable choke in a filter. Here, only series and parallel filters are shown (FIGS. 64a and 64b, respectively), but it is implied that variable inductance can be used in many filter topologies.
[0174]
Further applications of the present invention will be described with particular reference to FIGS. 14 and 15, but a schematic symbol proposal is shown in FIG. In this application example, the voltage connector has a function as a voltage converter to which a secondary winding is added. An application example as a voltage regulator is also illustrated here, where the transformer connection and leakage reactance can be controlled via the control winding 4. A special feature of this system is that the transformer equation can be applied, while at the same time the magnetizing current can be controlled by changing the μr. Therefore, in this case, the characteristics of the transformer can be adjusted to some extent. With the DC excitation of one winding 2, the energy converted by the transformer can be obtained by μr, and thus by the change of magnetic flux in the magnetoresistive control core instead of the change of excitation. Thus, it is in principle possible to generate an AC voltage from a DC voltage due to the fact that the change in magnetizing current from the DC generator to this system can be converted to the secondary winding.
[0175]
Another application example of the present invention is shown in FIGS. Here, a variable reluctance as a control core is surrounded or contained by one or more separate cores with separate windings. As shown in FIG. 55, the first magnetoresistive control core and the second core are designed as a closed magnetic circuit and are juxtaposed. Reference is also made to FIG. 65 showing an equivalent electrical circuit.
[0176]
FIG. 55 shows how the magnetic flux of the present invention travels in the core. It should be emphasized that the magnetic flux in the control core is coupled to the magnetic flux in the working core via a winding that houses both cores. In this system, the conversion of electrical energy can be controlled by the magnetic flux interrupted between the control core and the working core. Since the magnetic flux between the two cores is mutually coupled by Faraday's induction law, the functional relationship between the primary side equation and the secondary side equation is controlled by the coupling between the two magnetic fluxes. In linear applications, the voltage and current conversion between the primary and secondary windings can be controlled by changing the reluctance in the control core, so that the term of reluctance control transformer can be introduced here. forgiven. For switch embodiments, a magnetoresistive control switch term can be introduced.
[0177]
Next, the magnetic flux coupling between the primary or first main winding 2 and the secondary or second main winding 3 will be described. The windings 2 housed here in both the control core 24 and the core 25, which are magnetoresistive controlled, establish a magnetic flux in both cores. From the self-inductance L1 when the current I1 passes through the (winding) 2, it shows how much magnetic flux (winding) 2 is generated or how many flux turns are generated in the core . The mutual inductance between the primary winding 2 and the secondary winding 3 indicates how many flux turns are established by 2, and I1 is turned around the winding 2 and the secondary winding 3 It shows the state.
[0178]
Of course, the main core 25 is expected to be magnetoresistive controlled, but for the sake of simplicity, reference is here made to a system with the main core 25 having a constant magnetoresistance and the control core 24 having a variable magnetoresistance. I will decide.
[0179]
The magnetic flux lines follow a path that exhibits maximum permeance (maximum permeability), that is, maximum magnetic resistance.
[0180]
55 and 65, the leakage magnetic field in the main windings 2 and 3 is not considered. FIG. 55 shows a simplified model of a transformer in which the primary winding 2 and the secondary winding 3 are each wound around a transformer leg, while in practice both windings are wound on the same transformer leg. In this case, for example, the outer ring core in the main core 25 is wound around the secondary windings 3 distributed along the entire core 25. Similarly, the primary winding 2 is wound around the main core 25 and the control core 24 disposed concentrically within the main core.
[0181]
FIG. 65 shows a simplified magnetoresistive model for a device according to the present invention.
[0182]
FIG. 65a shows a simplified electrical equivalent circuit for a connector according to the present invention with the magnetic resistance replaced by an inductance.
[0183]
The current in the primary winding 2 generates a magnetic flux in the cores 24 and 25:

here:
Φp = total magnetic flux established by the current in winding 2
Φk = total magnetic flux traveling through the control core 24
Φl = a part of the total magnetic flux traveling through the main core 25
Since the leakage flux in the main core 24 and the control core 25 is ignored,

To some extent, Φk can be regarded as a controlled leakage flux.
[0184]
Based on FIG. 65, a greatly simplified electrical equivalent circuit for the magnetic circuit shown in FIG. 65b can be formulated.
[0185]
Thus, FIG. 65b shows the principle of a magnetoresistive control coupler, where the inductance Lk absorbs the voltage from the primary side.

[0186]
This inductance is controlled by the variable reluctance in the control core 24, and as a result, due to the sinusoidal steady voltage applied to the primary winding, the connection or voltage division is shown in Equation 43 as shown in Equation 43. Is approximately equal to the ratio between.

[0187]
When the control core 24 is saturated, Lk is very small compared to Lm and the voltage division is based on the ratio between the turns N1 / N3. When the control core is in the OFF state, Lk is large and the voltage conversion to the secondary side is prevented in the same range.
[0188]
The magnetization states of both cores with respect to applied voltage and frequency are evaluated so that the main core 25 and the control core 24 each absorb the full time voltage integral separately without reaching saturation. In this model, the iron areas of the control core and the working core are equal, but this is not considered to limit the invention.
[0189]
Since the control core 24 does not become saturated due to the main winding 2, the control core 24 can be reset independently of the acting magnetic flux B1 (H1), thereby achieving the object by the present invention realizing a magnetic switch. it can. If necessary, the main core 25 can only be reset after one pulse or half of the period until the required MMF returns to the second half period only to correct the distortion in the magnetizing current.
[0190]
In the switching application example, when the switch is off, that is, when the magnetic flux of the primary winding 2 is distributed between the control core 24 and the working core 25, the magnetic flux coupling between the primary winding 2 and the secondary winding 3. Is very small and a very small energy shift is generated in the primary winding 2 and the secondary winding 3.
[0191]
When the switch is on, that is, when the magnetic resistance in the control core 24 is very small (μr = 10 to 50) and approaches the magnetic resistance of the air coil, the primary winding 2 and the secondary winding 3 You will get very good flux coupling and energy conversion between.
[0192]
Therefore, an important application of the present invention is a frequency converter with a DC-AC or AC-DC converter that uses a magnetoresistive control switch in the magnetoresistive control switch and the conventional frequency converter connection and rectifier connection. is there.
[0193]
A variation of the frequency converter can be realized by applying a small sine voltage from each phase in the three-phase system, each connected to a separate magnetoresistive control core, which in turn is connected to the additional core and the magnetoresistive control core. And is coupled to one or more additional cores that are magnetically coupled to the magnetoresistive control core by a common winding. Next, a part of the sine voltage is connected from the magnetoresistive control core to the additional core, and a voltage having a different frequency is generated.
[0194]
A DC-AC converter can be realized by connecting a DC voltage to the main winding housed in the working core, at which point the working core is wound around the secondary winding and the magnetic flux between the working core and the control core. A sinusoidal voltage can be obtained by changing the coupling sinusoidally.
[0195]
FIG. 66 shows the connections for the magnetic switch. Of course, this also acts as an adjustable transformer.
[0196]
67 and 67a show an example of a three phase design. Of course, all other three-phase rectifier connections are possible. By connecting a diode bridge or a respective diode to a respective outlet in the 12-pulse connector, an adjustable rectifier is obtained.
[0197]
In applications as adjustable transformers, it is emphasized that the dimensions of the magnetoresistive control core are determined by the range of adjustments required for transformers for voltages (0-100% or 80-110%) Must.
[0198]
Figure 67b shows a connector in the frequency converter for converting the input frequency to a randomly selected output frequency, and a portion of the phase voltage generated from the 6 or 12 pulse transformer for each motor phase. The use of a device according to the invention intended to operate an asynchronous motor for adding is shown (67b).
[0199]
FIG. 68 shows a device used as a switch in a UFC (unrestricted frequency converter by forced rectification).
[0200]
FIG. 69 shows a circuit comprising six devices 28-33 according to the present invention. The devices 28-33 are used as frequency converters, and the period of the generated voltage consists of a part of the fundamental frequency. This forms a positive new half-cycle in the new sine voltage, followed by only a positive half-cycle or part of a half-cycle of the sine voltage to form a negative half-cycle or part of a negative half-cycle. It works by creating a negative half-cycle in the new sinusoidal voltage. In this method, a sine voltage is generated at a frequency between 10% and 100% of the fundamental frequency. This converter operates as a soft start because the voltage at the output is adjusted via magnetoresistive control of the connection between the primary and secondary windings.
[0201]
In FIG. 69, if the first half cycle is allowed by connector number 28 (main winding 2), the current flowing through the secondary winding (main winding 3) in the same connector is the secondary winding in connector number 29. The wire (main winding 3) is rectified, and from 29 to 28 and so on.
[0202]
FIG. 70 shows the use of the device according to the invention as a DC-AC converter. Here, the main winding 2 in the connector is excited by the DC voltage U1. This voltage establishes a magnetic field H1 (B1) in both the control core 24 and the main core 25 (not shown). The number of turns N1, N2, N3 and the area of the iron are designed in such a way that no core is saturated in steady state. In the event of transmission of the control signal (i.e. excitation of the control winding 4) to the control core 24, its magnetic flux B2 (H2) is transferred to the main core 25 and within this core 25 in the magnetic flux B1 (H1) The change is designed in such a way that a voltage is induced in the secondary winding (main winding 3). By having a sinusoidal control current I2, a sinusoidal voltage can be generated on the secondary side (main winding 3) at the same frequency as the control voltage U1.
[0203]
FIG. 70b shows the use of the present invention as a converter with a change in magnetoresistance.
[0204]
FIG. 71 shows the use of the device according to the invention as an AC-DC converter. The same control principle is used here as described above in the description of the frequency converter of FIG. FIG. 71b shows a diagram of the input and output voltage time of the device.
[0205]
As described above, the voltage connector according to the present invention has substantially no movable part for absorbing voltage between the generator and the load. The function of the connector is that the voltage between the generator and the load can be controlled from 0 to 100% with a small control current. The second function is simply to be a voltage switch. A further function is that a voltage curve can be formed and switched.
[0206]
The new technology based on the present invention can be used to upgrade existing diode rectifiers, but requires adjustment. For a 12-pulse or 24-pulse rectification system, the voltage in the system can be balanced in a simple manner while maintaining 0-100% controllable rectification.
[0207]
For the magnetic material encompassed by the present invention, it is selected on the basis of cost / benefit factors. Cost is linked to several parameters such as market availability, productivity of the various solutions selected and price. Profit elements are based on electrotechnical elements and materials are required including material type and magnetic properties. Magnetic properties that are considered important include hysteresis loss, saturation flux level, permeability, magnetization capacity and magnetostriction in the two main directions of the material. The electrical unit frequency, voltage and power to the energy source and user encompassed by the present invention are determined for material selection. Suitable materials include the following:
a) Iron-silicon steel: a piece having a thickness of about 0.1 mm to 0.3 mm and a width of 10 mm to 1100 mm and wound on a coil. Perhaps a large core is most preferred considering the price and manufacturing technology already developed. This is for use at a low frequency.
b) Iron-nickel alloy (permalloy) and / or iron-cobalt alloy (permendur), produced as a piece and wound on a coil. These are alloys with special magnetic properties, whose subgroups have developed very special properties.
c) Amorphous alloy, metaglass: a thickness of about 20 μm to 50 μm, a width of 4 to 200 mm, and wound on a coil. Very high permeability, very low loss can be made with almost zero magnetostriction. There are countless types such as those based on iron and those based on cobalt. Great property but expensive.
d) Soft ferrite: A specific form of sintered body developed for the converter industry. Used at high frequency due to small loss. Low magnetic flux density. Low loss. There are limitations on the dimensions that can be physically relied upon.
e) Compressed powder core: Compressed iron powder alloy with a specific shape developed for specific applications. Low permeability, currently up to about 400-600. Low loss, but high magnetic flux density. Can generate very complex shapes.
[0208]
All sintered bodies, press-molded cores are suitable for the present invention without the need for a special magnetic field coupler, since the actual shape can be made in a way that a closed magnetic circuit can be obtained for a suitable magnetic field. The topology can be executed.
[0209]
If the core is made on the basis of a rolled sheet metal, the core must be supplemented by one or more magnetic field couplers.
[Brief description of the drawings]
FIG. 1 is a diagram showing a basic principle of the present invention and a first embodiment thereof.
FIG. 2 is a diagram showing a basic principle of the present invention and a first embodiment thereof.
FIG. 3 is a schematic diagram of an embodiment of an apparatus according to the present invention.
FIG. 4 shows different areas of magnetic flux forming part of the device according to the invention.
FIG. 5 is a first equivalent circuit diagram of an apparatus according to the present invention.
FIG. 6 is a simplified block diagram of an apparatus according to the present invention.
FIG. 7 is a diagram showing magnetic flux versus current.
FIG. 8 shows magnetization curves and domains for the magnetic material of the device according to the invention.
FIG. 9 shows magnetization curves and domains for the magnetic material of the device according to the invention.
FIG. 10 is a diagram showing magnetic flux densities for a main winding and a control winding.
FIG. 11 is a diagram showing a second embodiment of the present invention.
FIG. 12 shows the same second embodiment of the present invention.
FIG. 13 is a cross-sectional view of a second embodiment.
FIG. 14 is a cross-sectional view of a second embodiment.
FIG. 15 is a diagram showing another embodiment of the magnetic field coupler of the second embodiment of the present invention.
FIG. 16 is a diagram showing another embodiment of the magnetic field coupler of the second embodiment of the present invention.
FIG. 17 is a diagram showing another embodiment of the magnetic field coupler of the second embodiment of the present invention.
FIG. 18 is a diagram showing a different embodiment of the magnetic field coupler according to the second embodiment of the present invention.
FIG. 19 is a view showing another embodiment of the tubular body of the second embodiment of the present invention.
FIG. 20 is a view showing another embodiment of the tubular body according to the second embodiment of the present invention.
FIG. 21 is a view showing another embodiment of the tubular body according to the second embodiment of the present invention.
FIG. 22 is a view showing another embodiment of the tubular body of the second embodiment of the present invention.
FIG. 23 is a view showing another embodiment of the tubular body according to the second embodiment of the present invention.
FIG. 24 is a view showing another embodiment of the tubular body of the second embodiment of the present invention.
FIG. 25 is a view showing another embodiment of the tubular body according to the second embodiment of the present invention.
FIG. 26 is a view showing another embodiment of the tubular body according to the second embodiment of the present invention.
FIG. 27 is a view showing a different embodiment of the tubular body of the second embodiment of the present invention.
FIG. 28 is a view showing another embodiment of the tubular body of the second embodiment of the present invention.
FIG. 29 is a view showing another embodiment of the tubular body according to the second embodiment of the present invention.
FIG. 30 is a view showing another embodiment of the tubular body according to the second embodiment of the present invention.
FIG. 31 is a diagram showing a different embodiment of the tubular body of the second embodiment of the present invention.
FIG. 32 is a view showing another embodiment of the tubular body of the second embodiment of the present invention.
FIG. 33 is a diagram showing different aspects of the magnetic field coupler according to the second embodiment of the present invention.
FIG. 34 is a diagram showing different aspects of the magnetic field coupler according to the second embodiment of the present invention.
FIG. 35 is a diagram showing different aspects of the magnetic field coupler according to the second embodiment of the present invention.
FIG. 36 is a diagram showing different aspects of the magnetic field coupler according to the second embodiment of the present invention.
FIG. 37 is a diagram showing different aspects of the magnetic field coupler according to the second embodiment of the present invention.
FIG. 38 is a diagram showing different aspects of the magnetic field coupler according to the second embodiment of the present invention.
FIG. 39 is a view showing an apparatus assembled according to the second embodiment of the present invention.
FIG. 40 is a cross-sectional view and a plan view of a third embodiment of the present invention.
FIG. 41 is a sectional view and a plan view of a third embodiment of the present invention.
FIG. 42 is a diagram showing a specific embodiment of a magnetic field coupler for use in the third embodiment of the present invention.
FIG. 43 is a diagram showing a specific embodiment of a magnetic field coupler for use in the third embodiment of the present invention.
FIG. 44 shows a specific embodiment of a magnetic field coupler for use in the third embodiment of the present invention.
FIG. 45 shows a third embodiment of the present invention for use as a transformer.
FIG. 46 is a cross-sectional and plan view of a fourth embodiment of the present invention for use as a magnetoresistive controlled flux coupling transformer.
FIG. 47 is a cross-sectional and plan view of a fourth embodiment of the present invention for use as a magnetoresistive controlled flux coupling transformer.
FIG. 48 is a diagram showing a fourth embodiment of the present invention applied to fit a powder-based magnetic material and thereby without a magnetic field coupler.
FIG. 49 is a diagram showing a fourth embodiment of the present invention applied to fit a powder reference magnetic material and thereby without a magnetic field coupler.
50 is a sectional view taken along line VI-VI in FIG. 48. FIG.
51 is a cross-sectional view taken along line VI-VI in FIG. 48. FIG.
FIG. 52 shows a core applied to fit a powder-based magnetic material and thereby without a magnetic field coupler.
FIG. 53 shows a core that is applied to fit a powder-based magnetic material, thereby without a magnetic field coupler.
FIG. 54 is an “X-ray photograph” of a modification of the fourth embodiment of the present invention.
FIG. 55 shows a second variant of the device according to the invention together with the principle behind the possibility for transformer connection.
FIG. 56 shows a proposal of an electro-mechanical schematic symbol for a voltage connector according to the present invention.
FIG. 57 shows a proposal for block schematic symbols for voltage connectors.
FIG. 58 is a diagram showing a magnetic circuit not including a control winding and a control magnetic flux.
FIG. 59 shows a proposal of an electro-mechanical schematic symbol for a voltage converter according to the invention.
FIG. 60 shows a proposal of an electro-mechanical schematic symbol for a voltage converter according to the present invention.
FIG. 61 is a diagram in which the present invention is used in an AC circuit.
FIG. 62 shows the use of the present invention in a three phase system.
FIG. 63 is a diagram showing the use of the DC-DC converter as a variable choke.
FIG. 64 shows use as a variable choke in a filter with a capacitor.
FIG. 65 shows a simplified magnetoresistive model for a device according to the present invention and a simplified electrical equivalent diagram for a connector according to the present invention.
FIG. 66 is a diagram showing connections for a magnetic switch.
FIG. 67 is a diagram showing an example of three-phase use of the present invention.
FIG. 68 is a diagram showing a device used as a switch;
FIG. 69 is a circuit diagram comprising six devices according to the present invention.
FIG. 70 illustrates the use of a device according to the present invention as a DC-AC converter.
FIG. 71 illustrates the use of a device according to the present invention as an AC-DC converter.

Claims (20)

A first outer tubular body (20) and a second inner tubular body (21) which are concentric with each other and thus have a common axis (A1), each made of a magnetizable material and providing a magnetic closed circuit. ) , At least one first conductor (8) wound around both tubular bodies (20, 21) of at least one winding forming the first main winding (2), and both tubular bodies At least one second wound around a common axis (A1) of the tubular body of at least one winding, which is arranged in the gap (22) between (20, 21) and forms the control winding (4). Consisting of a conductor (9),
Or
A first outer tubular body (20) and a second inner tubular body (21) which are concentric with each other and thus have a common axis (A1), each made of a magnetizable material and providing a magnetic closed circuit. ) And a common shaft (A1) of the tubular body of at least one winding which is disposed in the gap (22) between the tubular bodies (20, 21) to form the first main winding (2). At least one second conductor wound around both tubular bodies (20, 21) of at least one winding forming at least one first conductor (8) turned and a control winding (4). Consisting of a conductor (9),
The winding axis (A2) of one or more windings of the first main winding (2) is provided with a control winding (4 for the purpose of providing orthogonal magnetic fields (H1, B1 and H2, B2 respectively) of the body (1). ) Perpendicular to the winding axis (A4) of one or more windings, thereby magnetizing the magnetic field (H1, B1) of the main winding (2) by the magnetic field (H2, B2) of the control winding (4) A magnetic induction type current or voltage regulator for adjusting the properties of possible substances,
Both tubular bodies (20, 21) are made from a wound foil of magnetic material,
The regulator is a closed magnetic circuit for orthogonal magnetic fields (H1, B1, H2, B2) by means of both tubular bodies (20, 21), the first magnetic coupling element (10) and the second magnetic coupling element (11). A magnetic induction type current or voltage regulator characterized in that the first and second magnetic coupling elements are magnetically coupled to the respective end faces of both tubular bodies (20, 21). The first magnetic field coupling element (10) and the second magnetic field coupling element (11) are each composed of an air gap (13), and facilitate the insertion of the first electric conductor (8) or the second electric conductor (9). The magnetic induction type current or voltage regulator according to claim 1, wherein the magnetic path of the magnetic field H1 (B1) from the first conductor (8) and the second conductor (9) is blocked. One third conductor (27) wound as one winding forming the third main winding (3) is provided, and one or a plurality of winding axes (A3) of the third main winding (3) ) Coincides with or is parallel to the winding axis (A2) of one or more windings of the first main winding (2), and thus the first main winding (2) and the third main winding ( 3. Transformer action is provided between the first main winding (2) and the third main winding (3) when at least one of 3) is excited. Magnetic induction type current or voltage regulator as described. One third conductor (27) wound as one winding forming the third main winding (3) is provided, and one or a plurality of winding axes (A3) of the third main winding (3) ) Coincides with or is parallel to the winding axis (A4) of one or more windings of the control winding (4), and therefore at least of the third main winding (3) and the control winding (4). Magnetic induction type according to claim 1 or 2, characterized by providing a transformer action between the third main winding (3) and the control winding (4) when one is excited. Current or voltage regulator. Providing an outer core (25) attached to the outer side of the first outer tubular body (20), and the tubular bodies (20, 21) and the outer core (25) are concentric with each other; An additional tubular body having a common axis (A1),
The magnetic induction type current or voltage regulator according to any one of claims 1 to 4. One third conductor (27) wound around the outer core (25) as one winding forming the third main winding (3),
The winding axis (A3) of one winding or a plurality of windings of the third main winding (3) coincides with the winding axis (A2) of one or a plurality of windings of the first main winding (2). Parallel, so when at least one of the first main winding (2) and the third main winding (3) is excited, the first main winding (2) and the third main winding (3) Providing transformer action during
Or
The winding axis (A3) of one or more windings of the third main winding (3) is coincident with or parallel to the winding axis (A4) of one or more windings of the control winding (4). There, therefore, when at least one of the third main winding (3) and the control winding (4) is excited, a transformer action between the third main winding (3) and the control winding (4). The magnetic induction type current or voltage regulator according to claim 5, wherein the magnetic induction type current or voltage regulator is provided. The outer core (25) consists of several annular members (25 ′, 25 ″, etc.), and the first main winding (2) and / or the third main winding (3) are arranged around each annular member. 7. The magnetic induction type current or voltage regulator according to claim 5, wherein each winding is formed. The outer core (25) consists of several annular members (25 ', 25 ", etc.), and a control winding (4) and / or a third main winding (3) is provided around each annular member. The magnetic induction type current or voltage regulator according to any one of claims 5 to 7, wherein a winding is formed. 9. As an element in a frequency converter that converts an input frequency to a randomly selected output frequency, intended for the operation of an asynchronous motor in a cycloconverter connection, according to any one of claims 1-8. A method using a magnetic induction type current or voltage regulator. As a connector in a frequency converter that converts the input frequency to a randomly selected output frequency, as well as the operation of an asynchronous motor, adding part of the phase generated from a 6 or 12 pulse transformer to the phase of each motor A method of using a magnetic induction type current or voltage regulator according to any one of claims 1 to 8 to do (FIG. 67b). As a DC to AC converter that converts the DC voltage / current into an AC voltage / current of a randomly selected output frequency, the inductance of the DC supply first main winding (2) to the primary winding (2) ( The magnetic energy stored in L1) is changed by the orthogonal control magnetic field (B2, H2) affected by the inductance, thereby causing the first in the voltage connector at a frequency equal to the frequency of the flux change / inductance change (FIG. 70). 9. A method of using a magnetic induction type current or voltage regulator according to any one of claims 1 to 8 to generate an AC voltage in a three main winding (3) or a secondary winding. 12. The magnetic induction type of claim 11, wherein three variable inductance voltage converters of this type are interconnected to generate a three-phase voltage with a randomly selected output frequency connected to the asynchronous machine. To use the current or voltage regulator. In order to convert AC voltage to DC voltage within the processing industry, the device is used as a magnetoresistive controlled variable transformer and its output voltage is magnetically connected in parallel or in series with an external or internal core with a separate secondary winding 3 or more such magnetoresistive controlled transformers for 6 or 12 pulse rectifier connections for the diode output stage (FIGS. 62 and 71, respectively). 9. A method of using a magnetic induction type current or voltage regulator according to any one of claims 1 to 8, which is connected to a known three-phase rectifier connection. Used in a rectifier to convert AC voltage to DC voltage for use within the processing industry, the device forms a voltage connector used as a variable inductance in series with the primary winding of a known transformer connection, and 9. Three or more such transformers connect to a three-phase rectifier connection for a 6 or 12 pulse rectifier connection for a diode output stage (FIG. 62). A method using the magnetic induction type current or voltage regulator described in 1. Since the device forms a magnetoresistive controlled variable transformer, its output voltage is magnetically connected in parallel or in series with an external or internal core with a separate secondary winding (Figs. 56, 63) Magnetic induction type current or voltage according to any one of claims 1 to 8 for an AC / DC or DC / AC converter used in a magnetic field of a switching power supply and reducing the size of the magnetic voltage converter. How to use a regulator. The method of using a magnetic induction type current or voltage regulator according to claim 15, characterized in that the filter of which the inductance forms part comprises a variable inductance (Fig. 63). Magnetic induction current or voltage according to any one of the preceding claims, wherein the device generates a linear variable inductance (Fig. 72) as an element in an adjustable voltage compensator in a high voltage distribution network. How to use a regulator. As an element in an adjustable reactive power compensator (VAR compensator), the device generates a linear variable inductance in connection with a known filter circuit, where at least one capacitor is included as an element, and magnetoresistive control A device in the form of a transformer is used as an element in a compensator connection, and the capacitance or inductance of the connection is automatically combined to the extent required to compensate for reactive power (FIGS. 64 and 64b). 9. A method of using a magnetic induction type current or voltage regulator according to any one of claims 1 to 8, characterized in that it is regulated. Method for using a magnetically induced current or voltage regulator according to any one of claims 1 to 8 in a system for magnetoresistive controlled direct conversion from AC voltage to DC voltage (Figs. 71 and 71a). . Method for using a magnetically induced current or voltage regulator according to any one of claims 1 to 8 in a system for magnetoresistive controlled direct conversion from DC voltage to AC voltage (Figs. 70 and 70a). .

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