JP4304999B2 - Three-phase armature winding and motor using the same - Google Patents
Three-phase armature winding and motor using the same Download PDFInfo
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【０００１】
【発明の属する技術分野】
本発明は、同相３コイルが連続する３相電機子巻線に関し、特に２種の線径の導体で巻くことで、巻線占積率を低下させることなく巻線ターン数に自由度を持たせた３相電機子巻線およびそれを用いたモータに関する。
【０００２】
【従来の技術】
従来の同相３コイルが連続する３相電機子の巻線を図６に示す。図６（ａ）の電機子巻線の側断面図に示すように、連続する３つのＵ相巻線のターン数Ｎｕ１、Ｎｕ２、Ｎｕ３は、
Ｎｕ１＝Ｎｕ２＝Ｎｕ３
の関係になっている。
相順は、３コイルのグループで、Ｕ相、Ｖ相、Ｗ相の順番の巻線配置となっていて、図６（ｂ）の結線図に示すようになっている。図７は、図７（ａ）が各導体に電流を流した場合のアンペアターンベクトル（ＡＴｕ、ＡＴｗ、等）を示している。
この場合の、巻線係数Ｋｗは、次の（１）式で求められる。
（２）式は（１）式を用いた高調波γ＝１（基本波）の場合のＫｗ（１）値の計算式である。
図７（ｂ）は、その各高調波（γ：１〜２１）における、巻線係数Ｋｗのリストを示すものであり、第２項「従来Ｋｗ」がこの場合の計算値である。
また、こうした３相電機子巻線の使用例としては、特許文献１に開示の「リニアモータ」がある。図８はリニアモータの側面断面図であり、可動子８３の分割された各ブロックコア３１、３２、３３が相互に界磁磁石８１のピッチＰｍの２／３（電機角で１２０°）の間隔片８６によって隔離され、これに応じて各ブロックコアの電機子コイル８５を相互に電機角で１２０°の位相差で巻回すことにより、各ブロックコアの端効果によって発生するコギング推力ＴＣ１、ＴＣ２、ＴＣ３は、図９に示すように１２０°の位相差が生じ、その和をゼロに相殺することができ、鎖交磁束を最大にできる。
【０００３】
【特許文献１】
ＷＯ９９／４１８２５号公報（第１１頁、図１、図３）
【０００４】
【発明が解決しようとする課題】
しかしながら、上記特許文献１記載の発明にあっては、以下のような問題があった。
コイル寸法をＨ（高さ）×Ｗ（幅）、導体の線径φＩとする、ａＩ段×ｂＩ列の整列巻線の関係を、
Ｗ＝φＩ×ｂＩ列、ａＩ段＝Ｈ/φＩ（小数点切り捨て）
とした場合、 巻線の巻き回数を変化させようとしたとき、
ｂＪ列＝Ｗ/φＪ （小数点切り捨て）
ａＪ段＝Ｈ/φＪ （小数点切り捨て）
の関係として、占積率同一という条件の場合、
仮に、φＩ＝φ1.5ｍｍ、ａＩ段×ｂＩ列＝２０段×２列（４０ターン）で、１相グループのトータル巻き回数Ｗ＝４０ターン×３コイル＝１２０ターンのものを、これ以上に巻線を巻き込む（Kｔを大きく設計）とき、例えば、
φＪ＝φ1.0ｍｍ、ａＩ段×ｂＩ列＝３０段×３列（９０ターン）としたら、１相グループのトータル巻き回数Ｗ＝９０ターン×３コイル＝２７０ターンとなり、巻線巻回数の飛びが、２．２５倍になる場合があって、巻線設計の自由度が小さく、ユーザの要求する出力特性に整合させることが困難であるという問題があった。
【０００５】
そこで、本発明は、同相３コイルの＃１（＝＃３）コイルと＃２等の線径と巻回数を変えることによって、巻回数の飛びの中間的な巻回数が得られるようにして設計自由度が大きくとれるようにすると共に、界磁磁石の磁石幅をそれぞれ最適化することで出力特性の自由度を高くし、トルクリップルを軽減できる３相電機子巻線およびそれを用いたモータを提供することを目的としている。
【０００６】
【課題を解決するための手段】
上記の課題を解決するため、請求項１記載の３相電機子巻線の発明は、３相電機子巻線が界磁磁石に対して相対移動する方向にそれぞれ第１コイル・第２コイル・第３コイルの順に配置されて成るコイルグループが全て同相コイルで直列接続されている３相平衡巻線による３相電機子巻線であって、前記第１コイル・第２コイル・第３コイルのそれぞれの巻き回数ｎ１・ｎ２・ｎ３がｎ１＝ｎ３、ｎ１≠ｎ２の関係にある３相電機子巻線であって、
前記第１コイル・第３コイルの線径と前記第２コイルの線径とが異なるものであり、かつ、ターン数と線径を変えることによりこれら２種類のコイルから成る３相電機子巻線の巻線係数の各高調波のうち、推力の中心となる基本波成分が巻線係数０．９４５に対して約±１０％の範囲内に入るものとしたことを特徴とする。
請求項２記載の発明は、請求項１記載の３相電機子巻線において、３相電機子巻線が界磁磁石に対して相対移動する方向に前記第２コイルの線径φａの導体がｂ２列で並ぶ場合のφａ×ｂ２をコイル幅Ｗとし、相対移動する方向に対して垂直方向に前記第２コイルの導体がａ２段で整列重なる場合のφａ×ａ２をコイル高さＨとしたとき、
線径φｂ（φｂ＜φａ）の前記第１コイルの導体によるｂ１列およびａ１段が
ｂ１列＝Ｗ／φｂ （小数点切り捨て）
ａ１段＝Ｈ／φｂ （小数点切り捨て）
となるように前記線径φｂを選定したことを特徴とする。
請求項３記載の発明は、請求項１記載の３相電機子巻線において、３相電機子巻線が界磁磁石に対して相対移動する方向に前記第２コイルの線径φａの導体がｂ２列で並ぶ場合のφａ×ｂ２をコイル幅Ｗとし、相対移動する方向に対して垂直方向に前記第２コイルの導体がａ２段で整列重なる場合のφａ×ａ２をコイル高さＨとしたとき、
線径φｂ（φｂ＞φａ）の前記第１コイルの導体によるｂ１列およびａ１段が
ｂ１列＝Ｗ／φｂ （小数点切り捨て）
ａ１段＝Ｈ／φｂ （小数点切り捨て）
となるように前記線径φｂを選定したことを特徴とする。
このような構成の３相電機子巻線によれば、同相３コイルの＃１（＝＃３）コイルと＃２コイルの線径と巻回数を変えることによって、従来方式の巻回数の飛びの中間的な巻き回数が得られることとなり、出力特性の自由度が改善される。
【０００７】
【発明の実施の形態】
以下、本発明の実施の形態について図に基づいて説明する。
図１は本発明の実施の形態に係る３相電機子巻線の側断面図である。
図２は図１に示す各スロット内導体の特性図で、（ａ）は図１の場合の各相導体に電流を流した時に推力を発生する出力特性を、コイル電流（アンペアＡ）とコイルの巻数（ターンＴ）の積で表すアンペアターンＡＴのベクトル表示としたアンペアターンベクトル図であり、（ｂ）は図１の場合の各高調波γに対する巻線係数Ｋｗ値が記載されたリストである。
図３は図１に示すＮｕ２のターン数が大きい場合の３相電機子巻線の側面図である。
図４は図３に示す各スロット内導体の特性図で、（ａ）は図３の場合の各相導体に電流を流した時に推力を発生する出力特性を、コイル電流（アンペアＡ）とコイルの巻数（ターンＴ）の積で表すアンペアターンＡＴのベクトル表示としたアンペアターンベクトル図であり、（ｂ）は図３の場合の各高調波γに対する巻線係数Ｋｗ値が記載されたリストである。
図５は図１、図３に示す３相電機子巻線の速度−推力特性を示す図である。
図１において、１はコアティース間のスロットスペース、２は電機子コア、３はコイルボビン、４は界磁ヨーク、５は磁石カバー、６は界磁磁石、７はコイルを示している。
【０００８】
つぎに動作について説明する。
図１（ａ）は３相電機子巻線の側断面図で、図１（ｂ）にその結線図を示す。相順は、３コイルのグループでＵ相、Ｖ相、Ｗ相の順番の巻線配置となる。そのＵ相の３コイルの巻線ターン数Ｎｕ１、Ｎｕ２、Ｎｕ３は、
（Ｎｕ１＝Ｎｕ３）＞Ｎｕ２
として、Ｎｕ２の導体線径φａを
φａ＝φ１．５ｍｍ ａ２段×ｂ２列＝２０段×２列（４０ターン）として、Ｎｕ１＝Ｎｕ３の導体線径φｂを、
φｂ＝φ１．０ｍｍとすると、ｂ１列＝Ｗ／φｂ、ａ１段＝Ｈ／φｂより、
ａ１段×ｂ１列＝３０段×３列（９０ターン）
となり、Ｕ相グループのトータル巻き回数Ｗは、
Ｗ＝Ｎｕ１＋Ｎｕ２＋Ｎｕ３＝９０＋４０＋９０＝２２０ターンとなる。
【０００９】
次に、図３は、図３（ａ）が側断面図で、図３（ｂ）が結線図であり。この場合の巻線ターンＮｕ１〜Ｎｕ３が、
（Ｎｕ１＝Ｎｕ３）＜Ｎｕ２
の場合であり、Ｎｕ２の導体線径φａを
φａ＝φ１．０ｍｍ ａ２段×ｂ２列＝３０段×３列（９０ターン）
Ｎｕ１＝Ｎｕ３の導体線径φｂを、
φｂ＝φ１．５ｍｍとすると、ａ１段×ｂ１列＝２０段×２列（４０ターン）となり、Ｕ相グループのトータル巻き回数Ｗは、
Ｗ＝Ｎｕ１＋Ｎｕ２＋Ｎｕ３＝４０＋９０＋４０＝１７０ターンとなる。
このようにして中間的な巻線ターンが可能になる。
【００１０】
次に、このようなコイルの出力特性については、図２に図１の場合の特性を示す。
先ず、図２（ａ）は図１の場合の各相導体に電流を流した時に推力を発生する出力特性を表すものとして、コイル電流（アンペアＡ）とコイルの巻数（ターンＴ）の積で表すアンペアターンＡＴのベクトル表示であるアンペアターンベクトル図であり、図２（ｂ）はその場合の各高調波γに対する巻線係数Ｋｗ値のリストである。
この場合の巻線係数Ｋｗは次の（３）、（４）式より算出される。
【００１１】
一方、図３に示した、（Ｎｕ１＝Ｎｕ３）＜Ｎｕ２、の場合の出力特性については、図４（ａ）にアンペアターンベクトル図を示し、図４（ｂ）は各高調波γに対する巻線係数Ｋｗのリストを示す。この場合の巻線係数Ｋｗは次の（５）式、（６）式により算出される。
【００１２】
以上、従来の３相平衡巻線による８Ｐ／９ｓｌｏｔ、１０ｐ／９ｓｌｏｔ等の巻線方式の場合は、巻線係数Ｋｗも大きくとれ、コギング・トルクも小さくなる利点があるが、反面グループ数も少なく、整列高密度巻線設計を行う場合に自由度が小さいという問題点があったが、本発明では（Ｎｕ１＝Ｎｕ３）＞Ｎｕ２、若しくは、（Ｎｕ１＝Ｎｕ３）＜Ｎｕ２、のターン数と、導体線径φａ、φｂを変えてターン数の飛びを埋める方式によって、図５に示すように、従来は巻線のターン数が１２０ターン→２７０ターン（２．２５倍）の飛び差があったものが、図１の場合は１２０ターン→２２０ターン（１．８３倍）、図３の場合は１２０ターン→１７０ターン（１．４倍）と言うように中間を埋める巻線ターン数の設計が可能になるので、出力特性の自由度が改善される。
【００１３】
次に、このように改善された巻線ターン数の出力特性の変化についての評価・検証と、更なる、改善策について、各図を参照して検討する。
図２（ｂ）又は図４（ｂ）の巻線係数Ｋｗのリストを参照すると、高調波γの項目中、推力の中心となる基本波Ｋｗ（１）成分については従来の０．９４５に対して、図１の例では０．９３６、図３の例では、０．９５７と約±１０％の範囲内に入っており、鎖交磁束係数に大きな変化はなく、巻線占積率も低下しない。
３次高調波については、相結線をＹ結線にすれば、推力波形（端子間誘起電圧波形）に現れないため、５次、７次の係数と、磁石幅との組み合わせを最適化することで推力波形（端子間誘起電圧波形）の高調波成分を低減させることができる。
また、図２（ｂ）の場合は、５次係数が、小さく、７次係数が大きいので、界磁磁束に含まれる７次成分が小さくなるように、磁石幅Ｗｍを図１（ａ）に示すように磁極ピッチλｐから、
Ｗｍ＝（６/７）λｐ
のピッチに変えた磁石界磁と組み合わせる。
さらに、図４（ｂ）の場合は、５次係数が、大きく、７次係数が小さいので、界磁磁束に含まれる５次成分が小さくなるように、図３（ａ）に示すように、
Ｗｍ＝（４/５）λｐ
の磁石界磁と組み合わせ改善している。
【００１４】
【発明の効果】
以上述べたように、本発明によれば、３つの直列接続される同相コイルを、配置順としてｃ１、ｃ２、ｃ３としたとき、それぞれの巻き回数をｎ１、ｎ２、ｎ３とした場合、（ｎ１＝ｎ３）≠ｎ２の関係に決め、巻線も２種類の線径の巻線を使用するようにしたので、従来技術の場合の中間的巻線ターン数にて設計することが可能になり、駆動ドライバ容量を規定した場合、出力特性の自由度を高くすることができるという効果がある。
また、界磁磁石の磁石幅を、それぞれ最適化することで、推力またはトルクリップル成分を軽減・改善することができるという効果もある。
【図面の簡単な説明】
【図１】本発明の実施の形態に係る３相電機子巻線の側断面図である。
【図２】図１に示す各スロット内導体の特性図で、（ａ）は図１の場合の各相導体に電流を流した時に推力を発生する出力特性を、コイル電流（アンペアＡ）とコイルの巻数（ターンＴ）の積で表すアンペアターンＡＴのベクトル表示としたアンペアターンベクトル図であり、（ｂ）は図１の場合の各高調波γに対する巻線係数Ｋｗ値が記載されたリストである。
【図３】図１に示すＮｕ２のターン数が大きい場合の３相電機子巻線の側断面図である。
【図４】図３に示す各スロット内導体の特性図で、（ａ）は図３の場合の各相導体に電流を流した時に推力を発生する出力特性を、コイル電流（アンペアＡ）とコイルの巻数（ターンＴ）の積で表すアンペアターンＡＴのベクトル表示としたアンペアターンベクトル図であり、（ｂ）は図３の場合の各高調波γに対する巻線係数Ｋｗ値が記載されたリストである。
【図５】図１、図３に示す３相電機子巻線の速度−推力特性を示す図である。
【図６】従来の３相電機子巻線の側断面図である。
【図７】図６に示す各スロット内導体の特性図で、（ａ）は従来の図６の場合の各相導体に電流を流した時に推力を発生する出力特性を、コイル電流（アンペアＡ）とコイルの巻数（ターンＴ）の積で表すアンペアターンＡＴのベクトル表示としたアンペアターンベクトル図であり、（ｂ）は従来の場合の各高調波γに対する巻線係数Ｋｗ値が記載されたリストである。
【図８】従来のリニアモータの側断面図である。
【図９】図８に示すリニアモータのコギング推力の特性図である。
【符号の説明】
１ コアティース間のスロットスペース
２ 電機子コア
３ コイルボビン
４ 界磁ヨーク
５ 磁石カバー
６ 界磁磁石
７ コイル[0001]
BACKGROUND OF THE INVENTION
The present invention relates to a three-phase armature winding in which three coils of the same phase are continuous, and in particular, by winding with a conductor of two kinds of wire diameters, the number of turns of the winding is flexible without reducing the winding space factor. The present invention relates to a three-phase armature winding and a motor using the same.
[0002]
[Prior art]
FIG. 6 shows a winding of a three-phase armature in which a conventional three-phase in-phase coil is continuous. As shown in the side sectional view of the armature winding in FIG. 6A, the number of turns Nu1, Nu2, Nu3 of the three consecutive U-phase windings is:
Nu1 = Nu2 = Nu3
It has become a relationship.
The phase order is a group of 3 coils, and the winding arrangement is the order of U phase, V phase, and W phase, as shown in the connection diagram of FIG. 6B. FIG. 7 shows ampere-turn vectors (ATu, ATw, etc.) when FIG.
In this case, the winding coefficient Kw is obtained by the following equation (1).
Equation (2) is a formula for calculating the Kw (1) value when harmonic γ = 1 (fundamental wave) using equation (1).
FIG. 7B shows a list of winding coefficients Kw for each harmonic (γ: 1 to 21), and the second term “conventional Kw” is a calculated value in this case.
In addition, as a usage example of such a three-phase armature winding, there is a “linear motor” disclosed in
[0003]
[Patent Document 1]
WO99 / 41825 (
[0004]
[Problems to be solved by the invention]
However, the invention described in
The relationship of the aI stage × bI array of aligned windings, where the coil dimensions are H (height) × W (width) and the conductor wire diameter φI,
W = φI × bI column, aI stage = H / φI (decimal point truncation)
When trying to change the number of winding turns,
bJ row = W / φJ (decimal point truncation)
aJ stage = H / φJ (decimal point truncation)
In the case of the condition that the space factor is the same,
Temporarily, φI = φ1.5mm, aI stage x bI row = 20 stages x 2 rows (40 turns), and the total number of windings of one phase group W = 40 turns x 3 coils = 120 turns When winding a wire (designing Kt large), for example,
If φJ = φ1.0mm, aI stage × bI row = 30 steps × 3 rows (90 turns), the total number of windings for one phase group is W = 90 turns × 3 coils = 270 turns, and the number of winding turns jumps. 2.25 times, there is a problem that the degree of freedom in designing the winding is small and it is difficult to match the output characteristics required by the user.
[0005]
Therefore, the present invention is designed so that an intermediate number of turns can be obtained by changing the wire diameter and the number of turns of # 1 (= # 3) coil of # 3 (in-phase) coil and # 2 etc. A three-phase armature winding that can increase the degree of freedom and increase the degree of freedom of output characteristics by optimizing the magnet width of each field magnet to reduce torque ripple, and a motor using the same. It is intended to provide.
[0006]
[Means for Solving the Problems]
In order to solve the above problems, the invention of a three-phase armature winding according to
A three-phase armature winding in which the wire diameters of the first coil and the third coil are different from the wire diameter of the second coil, and these two types of coils are formed by changing the number of turns and the wire diameter . Among the harmonics of the winding coefficient, the fundamental wave component that is the center of thrust falls within a range of about ± 10% with respect to the winding coefficient 0.945.
According to a second aspect of the present invention, in the three-phase armature winding according to the first aspect, the conductor having the wire diameter φa of the second coil is in a direction in which the three-phase armature winding moves relative to the field magnet. When φa × b2 arranged in the b2 row is a coil width W, and φa × a2 when the conductor of the second coil is aligned and overlapped in a2 steps in a direction perpendicular to the direction of relative movement is a coil height H ,
B1 row and a1 stage by the conductor of the first coil of wire diameter φb (φb <φa) are b1 row = W / φb (decimal point truncation)
a1 stage = H / φb (decimal point truncation)
The wire diameter φb is selected so that
According to a third aspect of the present invention, in the three-phase armature winding according to the first aspect, the conductor having the wire diameter φa of the second coil in a direction in which the three-phase armature winding moves relative to the field magnet. When φa × b2 arranged in the b2 row is a coil width W, and φa × a2 when the conductor of the second coil is aligned and overlapped in a2 steps in a direction perpendicular to the direction of relative movement is a coil height H ,
B1 row and a1 stage by the conductor of the first coil of wire diameter φb (φb> φa) are b1 row = W / φb (decimal point truncation)
a1 stage = H / φb (decimal point truncation)
The wire diameter φb is selected so that
According to the three-phase armature winding having such a configuration, the number of turns of the conventional method can be reduced by changing the wire diameter and the number of turns of the # 1 (= # 3) coil and the # 2 coil of the in-phase three coils. An intermediate number of windings can be obtained, and the degree of freedom in output characteristics is improved.
[0007]
DETAILED DESCRIPTION OF THE INVENTION
Hereinafter, embodiments of the present invention will be described with reference to the drawings.
FIG. 1 is a side sectional view of a three-phase armature winding according to an embodiment of the present invention.
2 is a characteristic diagram of the conductor in each slot shown in FIG. 1. FIG. 2A shows the output characteristics that generate thrust when a current is passed through each phase conductor in FIG. 1, and the coil current (ampere A) and the coil. FIG. 2 is an ampere turn vector diagram showing a vector representation of an ampere turn AT expressed by the product of the number of turns (turn T) of FIG. 1, and (b) is a list in which the winding coefficient Kw value for each harmonic γ in the case of FIG. is there.
FIG. 3 is a side view of the three-phase armature winding when the number of turns of Nu2 shown in FIG. 1 is large.
FIG. 4 is a characteristic diagram of the conductor in each slot shown in FIG. 3, and FIG. 4A shows the output characteristics that generate thrust when a current is passed through each phase conductor in FIG. 3, the coil current (ampere A) and the coil. FIG. 4 is an ampere turn vector diagram showing a vector representation of an ampere turn AT expressed by the product of the number of turns (turn T), and FIG. 3B is a list in which the winding coefficient Kw value for each harmonic γ in the case of FIG. is there.
FIG. 5 is a diagram showing the speed-thrust characteristics of the three-phase armature winding shown in FIGS.
In FIG. 1, 1 is a slot space between core teeth, 2 is an armature core, 3 is a coil bobbin, 4 is a field yoke, 5 is a magnet cover, 6 is a field magnet, and 7 is a coil.
[0008]
Next, the operation will be described.
FIG. 1A is a side sectional view of a three-phase armature winding, and FIG. 1B shows a connection diagram thereof. The phase sequence is a winding arrangement in the order of U phase, V phase, and W phase in a group of 3 coils. The number of winding turns Nu1, Nu2, Nu3 of the three coils of the U phase is
(Nu1 = Nu3)> Nu2
Assuming that the conductor wire diameter φa of Nu2 is φa = φ1.5 mm a2 stages × b2 rows = 20 stages × 2 rows (40 turns), the conductor wire diameter φb of Nu1 = Nu3 is
If φb = φ1.0 mm, b1 row = W / φb, a1 stage = H / φb,
a1 row x b1 row = 30 rows x 3 rows (90 turns)
The total number of windings W of the U phase group is
W = Nu1 + Nu2 + Nu3 = 90 + 40 + 90 = 220 turns.
[0009]
Next, FIG. 3A is a sectional side view and FIG. 3B is a connection diagram. In this case, the winding turns Nu1 to Nu3 are
(Nu1 = Nu3) <Nu2
In this case, the conductor wire diameter φa of Nu2 is φa = φ1.0 mm a2 steps × b2 rows = 30 steps × 3 rows (90 turns)
The conductor wire diameter φb of Nu1 = Nu3 is
If φb = φ1.5 mm, a1 stage × b1 row = 20 stages × 2 rows (40 turns), and the total number of windings W of the U-phase group is
W = Nu1 + Nu2 + Nu3 = 40 + 90 + 40 = 170 turns.
In this way an intermediate winding turn is possible.
[0010]
Next, the output characteristics of such a coil are shown in FIG. 2 in the case of FIG.
First, FIG. 2 (a) is a product of the coil current (ampere A) and the number of turns of the coil (turn T), showing the output characteristics that generate thrust when a current is passed through each phase conductor in FIG. FIG. 2B is a list of winding coefficient Kw values for each harmonic γ in that case.
The winding coefficient Kw in this case is calculated from the following equations (3) and (4).
[0011]
On the other hand, regarding the output characteristics in the case of (Nu1 = Nu3) <Nu2 shown in FIG. 3, an ampere-turn vector diagram is shown in FIG. 4 (a), and FIG. 4 (b) is a winding for each harmonic γ. A list of coefficients Kw is shown. The winding coefficient Kw in this case is calculated by the following equations (5) and (6).
[0012]
As described above, in the case of a winding method such as 8P / 9 slot and 10p / 9 slot using the conventional three-phase balanced winding, there is an advantage that the winding coefficient Kw can be increased and the cogging torque is reduced, but the number of groups is also small. However, there is a problem that the degree of freedom is small when designing the aligned high-density winding. In the present invention, the number of turns of (Nu1 = Nu3)> Nu2 or (Nu1 = Nu3) <Nu2 and the conductor By changing the wire diameters φa and φb and filling the jump of the number of turns, as shown in FIG. 5, conventionally, the number of turns of the winding was 120 turns → 270 turns (2.25 times). However, in the case of FIG. 1, 120 turns → 220 turns (1.83 times), and in the case of FIG. 3, 120 turns → 170 turns (1.4 times) so that the number of winding turns filling the middle can be designed. So The degree of freedom of output characteristics is improved.
[0013]
Next, the evaluation and verification of the change in the output characteristics of the number of winding turns thus improved, and further improvement measures will be discussed with reference to each figure.
Referring to the list of winding coefficient Kw in FIG. 2B or FIG. 4B, the fundamental wave Kw (1) component that is the center of thrust in the item of harmonic γ is compared with the conventional 0.945. 1 is 0.936, and in the example of FIG. 3 is 0.957, which is within a range of about ± 10%. There is no significant change in the flux linkage coefficient, and the winding space factor is also reduced. do not do.
For the 3rd harmonic, if the phase connection is changed to the Y connection, it does not appear in the thrust waveform (inter-terminal induced voltage waveform). Therefore, by optimizing the combination of the 5th and 7th order coefficients and the magnet width Harmonic components of the thrust waveform (inter-terminal induced voltage waveform) can be reduced.
In the case of FIG. 2B, since the fifth order coefficient is small and the seventh order coefficient is large, the magnet width Wm is shown in FIG. 1A so that the seventh order component included in the field magnetic flux is reduced. As shown, from the magnetic pole pitch λp
Wm = (6/7) λp
Combined with the magnet field changed to the pitch.
Further, in the case of FIG. 4B, since the fifth order coefficient is large and the seventh order coefficient is small, as shown in FIG. 3A, the fifth order component included in the field magnetic flux is reduced.
Wm = (4/5) λp
It has been improved in combination with the magnet field.
[0014]
【The invention's effect】
As described above, according to the present invention, when three in-phase coils connected in series are c1, c2, and c3 in the arrangement order, the number of turns is n1, n2, and n3, (n1 = N3) ≠ n2 and the windings are made of two types of wire diameters. Therefore, it is possible to design with the number of intermediate winding turns in the case of the prior art, When the drive driver capacity is defined, there is an effect that the degree of freedom of output characteristics can be increased.
Further, by optimizing the magnet width of each field magnet, there is an effect that the thrust or torque ripple component can be reduced or improved.
[Brief description of the drawings]
FIG. 1 is a side sectional view of a three-phase armature winding according to an embodiment of the present invention.
2 is a characteristic diagram of the conductors in each slot shown in FIG. 1. FIG. 2 (a) is an output characteristic that generates a thrust when a current is passed through each phase conductor in FIG. 1, and a coil current (ampere A). FIG. 2 is an ampere turn vector diagram representing a vector of an ampere turn AT expressed by the product of the number of turns of the coil (turn T), and FIG. 3B is a list in which winding coefficient Kw values for each harmonic γ in FIG. It is.
FIG. 3 is a side sectional view of a three-phase armature winding when the number of turns of Nu2 shown in FIG. 1 is large.
4 is a characteristic diagram of the conductor in each slot shown in FIG. 3. FIG. 4 (a) shows the output characteristics that generate thrust when a current is passed through each phase conductor in the case of FIG. 3, coil current (ampere A). FIG. 4 is an ampere turn vector diagram representing a vector of an ampere turn AT expressed by a product of the number of turns of the coil (turn T), and FIG. 3B is a list in which a winding coefficient Kw value for each harmonic γ in the case of FIG. It is.
FIG. 5 is a diagram showing speed-thrust characteristics of the three-phase armature winding shown in FIGS. 1 and 3;
FIG. 6 is a side sectional view of a conventional three-phase armature winding.
7 is a characteristic diagram of the conductor in each slot shown in FIG. 6. FIG. 7 (a) is a graph showing the output characteristics that generate thrust when a current is passed through each phase conductor in the case of FIG. ) And the number of turns of the coil (turn T), an ampere turn vector diagram represented as a vector display of an ampere turn AT, and (b) describes the winding coefficient Kw value for each harmonic γ in the conventional case. It is a list.
FIG. 8 is a side sectional view of a conventional linear motor.
9 is a characteristic diagram of cogging thrust of the linear motor shown in FIG. 8. FIG.
[Explanation of symbols]
DESCRIPTION OF
Claims (3)
前記第１コイル・第３コイルの線径と前記第２コイルの線径とが異なるものであり、かつ、ターン数と線径を変えることによりこれら２種類のコイルから成る３相電機子巻線の巻線係数の各高調波のうち、推力の中心となる基本波成分が巻線係数０．９４５に対して約±１０％の範囲内に入るものとしたことを特徴とする３相電機子巻線。Three-phase armature windings are arranged in series in the order of the first coil, the second coil, and the third coil in the direction in which the three-phase armature winding moves relative to the field magnet. A three-phase armature winding using a balanced winding, wherein the number of turns n1, n2, and n3 of the first coil, the second coil, and the third coil is such that n1 = n3 and n1 ≠ n2. An armature winding,
A three-phase armature winding in which the wire diameters of the first coil and the third coil are different from the wire diameter of the second coil, and these two types of coils are formed by changing the number of turns and the wire diameter . Among the higher harmonics of the winding coefficient, the three-phase armature is characterized in that the fundamental wave component that is the center of thrust falls within the range of about ± 10% with respect to the winding coefficient 0.945 Winding.
線径φｂ（φｂ＜φａ）の前記第１コイルの導体によるｂ１列およびａ１段が
ｂ１列＝Ｗ／φｂ （小数点切り捨て）
ａ１段＝Ｈ／φｂ （小数点切り捨て）
となるように前記線径φｂを選定したことを特徴とする請求項１記載の３相電機子巻線。When the conductors having the wire diameter φa of the second coil are arranged in b2 rows in the direction in which the three-phase armature winding moves relative to the field magnet, φa × b2 is defined as the coil width W, and the relative movement direction When the coil height H is φa × a2 when the conductors of the second coil are aligned and overlapped at a2 steps in the vertical direction,
B1 row and a1 stage by the conductor of the first coil of wire diameter φb (φb <φa) are b1 row = W / φb (decimal point truncation)
a1 stage = H / φb (decimal point truncation)
The three-phase armature winding according to claim 1, wherein the wire diameter φb is selected so that
線径φｂ（φｂ＞φａ）の前記第１コイルの導体によるｂ１列およびａ１段が
ｂ１列＝Ｗ／φｂ （小数点切り捨て）
ａ１段＝Ｈ／φｂ （小数点切り捨て）
となるように前記線径φｂを選定したことを特徴とする請求項１記載の３相電機子巻線。When the conductors having the wire diameter φa of the second coil are arranged in b2 rows in the direction in which the three-phase armature winding moves relative to the field magnet, φa × b2 is defined as the coil width W, and the relative movement direction When the coil height H is φa × a2 when the conductors of the second coil are aligned and overlapped at a2 steps in the vertical direction,
B1 row and a1 stage by the conductor of the first coil of wire diameter φb (φb> φa) are b1 row = W / φb (decimal point truncation)
a1 stage = H / φb (decimal point truncation)
The three-phase armature winding according to claim 1, wherein the wire diameter φb is selected so that
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| Publication number | Priority date | Publication date | Assignee | Title |
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| WO2013098949A1 (en) | 2011-12-27 | 2013-07-04 | 株式会社安川電機 | Motor |
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| JP5841885B2 (en) * | 2012-04-06 | 2016-01-13 | ヤマハ発動機株式会社 | Linear motor |
| WO2014091609A1 (en) | 2012-12-13 | 2014-06-19 | 三菱電機株式会社 | Rotating electrical machine |
| JP2014158396A (en) * | 2013-02-18 | 2014-08-28 | Mitsubishi Electric Corp | Synchronous motor stator |
| CN108683319B (en) * | 2018-06-01 | 2020-12-11 | 哈尔滨理工大学 | Low-speed high-thrust-density cylindrical linear motor with double-layer fractional slot windings |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
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| WO2013098949A1 (en) | 2011-12-27 | 2013-07-04 | 株式会社安川電機 | Motor |
| US9172281B2 (en) | 2011-12-27 | 2015-10-27 | Kabushiki Kaisha Yaskawa Denki | Motor |
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